CN105281365A

CN105281365A - Diesel-storage type military alternating current mobile power station and power quality control method therefor

Info

Publication number: CN105281365A
Application number: CN201510689526.XA
Authority: CN
Inventors: 徐海亮; 马晓军; 廖自力; 魏曙光; 袁东; 刘春光
Original assignee: Academy of Armored Forces Engineering of PLA
Current assignee: Academy of Armored Forces Engineering of PLA
Priority date: 2015-10-21
Filing date: 2015-10-21
Publication date: 2016-01-27
Anticipated expiration: 2035-10-21
Also published as: CN105281365B

Abstract

本发明公开了一种柴储型军用交流移动电站及其电能质量控制方法。该新型电站包含柴油发电机组、锂电池、超级电容、三相可控整流器、双向DC-DC变换器和三相可控逆变器等主要部件；上述部件集成于一个军用标准方舱之内。通过对三相可控整流器、双向DC-DC变换器的改进控制，电站允许直流母线电压在一定范围内波动，该设计充分发挥了超级电容的高功率密度特性，同时降低了锂电池充放电的频率，延长了设备的使用寿命。本发明通过对三相可控逆变器控制策略的优化设计，实现了对电网谐波污染的有效治理，提高了军用交流移动电站的电能输出质量。The invention discloses a diesel storage type military AC mobile power station and a power quality control method thereof. The new power station includes main components such as diesel generator set, lithium battery, super capacitor, three-phase controllable rectifier, bidirectional DC-DC converter and three-phase controllable inverter; the above components are integrated in a military standard shelter. Through the improved control of the three-phase controllable rectifier and the bidirectional DC-DC converter, the power station allows the DC bus voltage to fluctuate within a certain range. This design gives full play to the high power density characteristics of the super capacitor, and at the same time reduces the charge and discharge of the lithium battery. frequency, prolonging the service life of the equipment. The invention realizes the effective control of the harmonic pollution of the power grid through the optimal design of the control strategy of the three-phase controllable inverter, and improves the power output quality of the military AC mobile power station.

Description

A diesel storage type military AC mobile power station and its power quality control method

技术领域technical field

本发明涉及一种移动电站，尤其涉及一种对供电品质要求较高的军用交流移动电站及其电能质量控制方法。The invention relates to a mobile power station, in particular to a military AC mobile power station with high requirements on power supply quality and a power quality control method thereof.

背景技术Background technique

军用交流移动电站在军事领域具有广泛用途，主要用以遂行雷达兵、通信兵、炮兵等兵种装备的电力保障任务。根据国家标准GJB235A-97《军用交流移动电站统用规范》的有关要求，额定功率为3～250kW的军用交流移动电站的在空载额定电压时畸变率应不大于10％或5％。近年来，随着脉冲雷达等大型军用电气设备的投入使用，传统的柴油发电机组为主的汽车电站已不能满足通信、测控设备的高品质用电需求，主要体现在以下几个方面：The military AC mobile power station has a wide range of uses in the military field, and is mainly used to perform power support tasks for radar troops, communication troops, artillery and other arms. According to the relevant requirements of the national standard GJB235A-97 "Universal Specifications for Military AC Mobile Power Stations", the distortion rate of military AC mobile power stations with a rated power of 3-250kW should not exceed 10% or 5% at no-load rated voltage. In recent years, with the use of large-scale military electrical equipment such as pulse radar, the traditional diesel generator-based automobile power station can no longer meet the high-quality power demand of communication and measurement and control equipment, which is mainly reflected in the following aspects:

首先，动态带载能力不强。本质上看，以油机为主的军用交流移动电站是典型的微网络，受负载功率波动影响较为明显，大功率用电设备的突加、突卸易引发电网波动，波及系统内其他负荷的运行安全，甚至导致系统失稳瘫痪。First of all, the dynamic load capacity is not strong. In essence, military AC mobile power stations dominated by diesel generators are typical micro-networks, which are more obviously affected by load power fluctuations. Sudden addition and unloading of high-power electrical equipment can easily cause grid fluctuations and affect other loads in the system. Safe operation, even lead to system instability and paralysis.

其次，“大马拉小车”的问题比较突出。目前我军测控、通信设备多位脉冲功率负载，其瞬时功率往往在平均功率2倍以上。由于不具备缓冲环节，现有军用交流移动电站通常以瞬时功率作为设计依据，致使油机的体积重量大幅增加。Secondly, the problem of "big horse-drawn carts" is more prominent. At present, the instantaneous power of multi-bit pulse power loads of military measurement and control and communication equipment is often more than twice the average power. Because there is no buffer link, the existing military AC mobile power station is usually designed based on instantaneous power, resulting in a substantial increase in the volume and weight of the oil generator.

再次，输出电能品质较差。传统军用交流移动电站只能通过调节励磁电流对输出电压的幅值、相位进行修正，但对于负载引起的电压不平衡、谐波畸变等典型故障则无能为力。上述典型电网故障如不加以治理，必将对系统内敏感设备的正常工作造成严重干扰，甚至导致设备损坏。Again, the output power quality is poor. Traditional military AC mobile power stations can only correct the amplitude and phase of the output voltage by adjusting the excitation current, but they are powerless to deal with typical faults such as voltage imbalance and harmonic distortion caused by loads. If the above-mentioned typical power grid faults are not dealt with, it will definitely cause serious interference to the normal operation of sensitive equipment in the system, and even cause equipment damage.

因此，开发一种具有电能质量管理功能的新型军用交流移动电站就显得尤为重要和紧迫。Therefore, it is particularly important and urgent to develop a new military AC mobile power station with power quality management functions.

发明内容Contents of the invention

本发明的目的是针对现有技术的不足，提供一种柴储型军用交流移动电站及其电能质量控制方法，满足军用通信设备、测控设备对交流移动电站的高品质供电需求。The purpose of the present invention is to address the deficiencies of the prior art, to provide a diesel storage type military AC mobile power station and its power quality control method, to meet the high-quality power supply requirements of military communication equipment and measurement and control equipment for the AC mobile power station.

本发明的目的是通过以下技术方案来实现的：一种柴储型军用交流移动电站主要包括以下组成部件：柴油发电机组、锂电池、超级电容、三相可控整流器、双向DC-DC变换器和三相可控逆变器；上述各组成部件集成于一个军用标准方舱之内，且各部件之间具有如下电气连接关系：柴油发电机组的三相交流电输出端，连接到三相可控整流器的输入端，三相可控整流器的输出端并联到直流母线上；锂电池的输出端，连接到双向DC-DC变换器的输入端(低压端)，双向DC-DC变换器的输出端(高压端)并联到直流母线上；超级电容直接并联到直流母线上；三相可控逆变器的输入端连接到直流母线上，三相可控逆变器的输出端连接到用电设备(负载)。本发明的一种柴储型军用交流移动电站的电能质量控制方法主要包括以下步骤：The purpose of the present invention is achieved through the following technical solutions: a diesel storage type military AC mobile power station mainly includes the following components: diesel generator set, lithium battery, super capacitor, three-phase controllable rectifier, bidirectional DC-DC converter and three-phase controllable inverter; the above-mentioned components are integrated in a military standard shelter, and the electrical connections between the components are as follows: the three-phase AC output terminal of the diesel generator set is connected to the three-phase controllable The input terminal of the rectifier and the output terminal of the three-phase controllable rectifier are connected in parallel to the DC bus; the output terminal of the lithium battery is connected to the input terminal (low voltage terminal) of the bidirectional DC-DC converter, and the output terminal of the bidirectional DC-DC converter (high-voltage side) connected to the DC bus in parallel; the supercapacitor is directly connected in parallel to the DC bus; the input terminal of the three-phase controllable inverter is connected to the DC bus, and the output terminal of the three-phase controllable inverter is connected to the electrical equipment (load). The power quality control method of a kind of diesel storage type military AC mobile power station of the present invention mainly comprises the following steps:

1.利用传感器采集以下信号：柴油发电机组输出的机侧三相交流电压U_gabc和机侧三相交流电流I_gabc，锂电池的输出电流(或锂电池的放电电流)I_dc，直流母线电压U_dc，三相可控逆变器输出的网侧三相交流电压u_nabc，直流侧负载电流I_load；1. Use the sensor to collect the following signals: the generator-side three-phase AC voltage U _gabc and the generator-side three-phase AC current I _gabc , the output current of the lithium battery (or the discharge current of the lithium battery) I _dc , and the DC bus voltage U _dc , grid-side three-phase AC voltage u _nabc output by the three-phase controllable inverter, and DC-side load current I _load ;

2.双向DC-DC变换器的作用是控制锂电池的电能充放，维持母线电压的稳定；根据锂电池的荷电状态Soc，将双向DC-DC变换器的控制模式划分为Boost、Buck两种，具体为：2. The function of the bidirectional DC-DC converter is to control the charging and discharging of the lithium battery and maintain the stability of the bus voltage; according to the state of charge Soc of the lithium battery, the control mode of the bidirectional DC-DC converter is divided into Boost and Buck. species, specifically:

2.1当锂电池的荷电状态Soc大于设定阈值Soc_min时，双向DC-DC变换器切换至Boost模式；反之，当Soc小于等于设定阈值Soc_min时，双向DC-DC变换器切换至Buck模式；2.1 When the state of charge Soc of the lithium battery is greater than the set threshold Soc _min , the bidirectional DC-DC converter switches to Boost mode; otherwise, when the Soc is less than or equal to the set threshold Soc _min , the bidirectional DC-DC converter switches to Buck model;

2.2Boost模式下，当直流母线电压U_dc的幅值低于设定阈值电压U_dcmin时，直流母线电压指令与直流母线电压U_dc的差值ΔU_dc送入电压环比例积分(PI)控制器，得到下功率管调制电压U_d，将U_d送入PWM模块，即可产生双向DC-DC变换器的下功率管T₂的触发信号S_d；反之直流母线电压U_dc的幅值高于等于设定阈值电压U_dcmin时，下功率管T₂的触发信号S_d设置为零；Boost模式下，双向DC-DC变换器的上功率管T₁的触发信号始终设置为零，即上功率管T₁处于闭锁状态；2.2 In Boost mode, when the amplitude of the DC bus voltage U _dc is lower than the set threshold voltage U _dcmin , the DC bus voltage command The difference ΔU _dc from the DC bus voltage U _dc is sent to the voltage loop proportional integral (PI) controller to obtain the modulation voltage U _d of the lower power tube, and U _d is sent to the PWM module to generate the bidirectional DC-DC converter _The trigger signal S _d of the lower power transistor T2 _; otherwise, when the amplitude of the DC bus voltage _{Udc is higher than or equal to the set threshold voltage Udcmin} _, the trigger signal S _d of the lower power transistor T2 is set to zero; in Boost mode, bidirectional The trigger signal of the upper power transistor T1 _of the DC-DC converter is always set to zero, that is, the upper power transistor T1 is in _a locked state;

2.3Buck模式下，锂电池的电流指令与锂电池的输出电流I_dc的差值ΔI_dc送入电流环比例积分(PI)控制器，得到上功率管调制电压U′_d；将U′_d送入与步骤2.2相同的PWM模块，即可产生上功率管T₁的触发信号S′_d；Buck模式下，下功率管T₂的触发信号始终为零，即下功率管T₂处于闭锁状态；2. In 3Buck mode, the current command of the lithium battery The difference ΔI _dc of the output current I _dc of the lithium battery is sent to the current loop proportional-integral (PI) controller to obtain the upper power tube modulation voltage U′ _d ; U′ _d is sent to the same PWM module as step 2.2, namely _The trigger signal _S'd of the upper power tube T1 can be generated _; in the Buck mode, the trigger signal of the lower power tube T2 is always zero, that is, the lower power tube T2 is in a locked state _;

3.三相可控整流器的作用是将柴油发电机组的输出电压由交流转换成直流，其控制采用基于空间矢量调制的直接功率控制方法，具体为：3. The function of the three-phase controllable rectifier is to convert the output voltage of the diesel generator set from AC to DC, and its control adopts the direct power control method based on space vector modulation, specifically:

3.1柴油发电机组输出的机侧三相交流电压U_gabc首先送入传统的数字锁相环PLL进行锁相，获得机侧三相交流电压的位置角θ_g、角频率ω_g和幅值U_g；3.1 The generator-side three-phase AC voltage U _gabc output by the diesel generator set is first sent to the traditional digital phase-locked loop PLL for phase-locking, and the position angle θ _g , angular frequency ω _g and amplitude U _g of the generator-side three-phase AC voltage are obtained ;

3.2柴油发电机组输出的机侧三相交流电压U_gabc、机侧三相交流电流I_gabc送入功率计算模块，得到柴油发电机组的输出有功功率P_g、输出无功功率Q_g；3.2 The generator-side three-phase AC voltage U _gabc and the generator-side three-phase AC current I _gabc output by the diesel generator set are sent to the power calculation module to obtain the output active power P _g and output reactive power Q _g of the diesel generator set;

3.3柴油发电机组的有功功率指令无功功率指令分别与其对应的输出有功功率P_g、输出无功功率Q_g作差，其差值ΔP_g、ΔQ_g分别送入功率环比例积分(PI)控制器，得到三相可控整流器的有功电压指令V_gd和无功电压指令V_gq；其中，柴油发电机组的有功功率指令无功功率指令计算方程为：3.3 Active power command of diesel generator set reactive power command Make difference with the corresponding output active power P _g and output reactive power Q _g respectively, and the difference ΔP _g and ΔQ _g are respectively sent to the power loop proportional-integral (PI) controller to obtain the active voltage command of the three-phase controllable rectifier V _gd and reactive voltage command V _gq ; among them, the active power command of diesel generator set reactive power command The calculation equation is:

$\{\begin{matrix} {P P}_{g g}^{* *} = = {U u}_{d d c c} \cdot \cdot {I I}_{l l o o a a d d} \\ {Q Q}_{g g}^{* *} = = 00 \end{matrix};;$

3.4步骤3.3得到的三相可控整流器的有功电压指令V_gd、无功电压指令V_gq分别加上各自的补偿项，得到三相可控整流器的有功控制电压U_cd、无功控制电压U_cq；具体计算方程为：3.4 The active voltage command V _gd and reactive voltage command V _gq of the three-phase controllable rectifier obtained in step 3.3 are respectively added with respective compensation items to obtain the active control voltage U _cd and reactive control voltage U _cq of the three-phase controllable rectifier ; The specific calculation equation is:

$\{\begin{matrix} {U u}_{c c d d} = = - - {V V}_{g g d d} + + (({U u}_{g g} - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {Q Q}_{g g})) \\ {U u}_{c c q q} = = {V V}_{g g q q} - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {P P}_{g g} \end{matrix};;$

式中：L_g为三相可控整流器的滤波电感；In the formula: L _g is the filter inductance of the three-phase controllable rectifier;

3.5利用步骤3.1获得的机侧三相交流电压的位置角θ_g对步骤3.4得到的有功控制电压U_cd、无功控制电压U_cq进行Park反变换，得到静止坐标系下的有功调节电压U_cα、无功调节电压U_cβ；3.5 Use the position angle θ _g of the machine-side three-phase AC voltage obtained in step 3.1 to perform inverse Park transformation on the active control voltage U _cd and reactive control voltage U _cq obtained in step 3.4 to obtain the active regulation voltage U _cα in the stationary coordinate system , reactive power regulation voltage U _cβ ;

Park反变换过程可表示为：The Park inverse transformation process can be expressed as:

$[\begin{matrix} {U u}_{c c α α} \\ {U u}_{c c β β} \end{matrix}] = = [\begin{matrix} {cosθ cosθ}_{g g} & {sinθ sinθ}_{g g} \\ - - {sinθ sinθ}_{g g} & {cosθ cosθ}_{g g} \end{matrix}] [\begin{matrix} {U u}_{c c d d} \\ {U u}_{c c q q} \end{matrix}];;$

3.6将步骤3.5得到的静止坐标系下的有功调节电压U_cα、无功调节电压U_cβ进行空间矢量调制(SVM)，即可获得三相可控整流器的开关信号s_a、s_b、s_c，实现对三相可控整流器的有效控制；3.6 Perform space vector modulation (SVM) on the active power regulation voltage U _cα and reactive power regulation voltage U _cβ in the stationary coordinate system obtained in step 3.5 to obtain the switching signals s _a , s _b , and s _c of the three-phase controllable rectifier , to realize the effective control of the three-phase controllable rectifier;

4.三相可控逆变器的作用是将直流电转换为负载所需的三相交流电，并对电网谐波污染进行治理，其控制方法为：4. The function of the three-phase controllable inverter is to convert the direct current into the three-phase alternating current required by the load, and to control the harmonic pollution of the power grid. The control method is as follows:

4.1生成三相可控逆变器的三相电压指令具体为：4.1 Generate the three-phase voltage command of the three-phase controllable inverter Specifically:

$\{\begin{matrix} {u u}_{n no a a}^{* *} = = M m \cdot &Center Dot; s the s i i n no (({ω ω}_{g g} \times \times t t + + {ω ω}_{00})) \\ {u u}_{n no b b}^{* *} = = M m \cdot \cdot s the s i i n no (({ω ω}_{g g} \times \times t t + + {ω ω}_{00} - - 22 π π / / 33)) \\ {u u}_{n no c c}^{* *} = = M m \cdot \cdot s the s i i n no (({ω ω}_{g g} \times \times t t + + {ω ω}_{00} + + 22 π π / / 33)) \end{matrix};;$

式中：M为相电压的幅值，且有ω₀为三相电压的初始相位角，一般可设置为零，即ω₀＝0；分别为的A相、B相、C相分量；In the formula: M is the amplitude of the phase voltage, and ω ₀ is the initial phase angle of the three-phase voltage, which can generally be set to zero, that is, ω ₀ =0; respectively A phase, B phase, C phase components of phase;

4.2参照步骤3.1，将步骤4.1生成的三相电压指令送入传统的数字锁相环PLL，得到三相可控逆变器的输出电压位置角θ_n；4.2 Referring to step 3.1, the three-phase voltage command generated in step 4.1 Send it into the traditional digital phase-locked loop PLL to get the output voltage position angle θ _n of the three-phase controllable inverter;

4.3利用步骤4.2得到的输出电压位置角θ_n分别对三相电压指令和网侧三相交流电压u_nabc进行Park变换，得到三相可控逆变器的网侧电压指令和网侧电压矢量u_ndq；4.3 Use the output voltage position angle θ _n obtained in step 4.2 to control the three-phase voltage command Perform Park transformation with the grid-side three-phase AC voltage u _nabc to obtain the grid-side voltage command of the three-phase controllable inverter and grid-side voltage vector u _ndq ;

以对三相电压指令的Park变换为例，其矩阵方程可以表示为：To the three-phase voltage command Take the Park transform as an example, its matrix equation can be expressed as:

$[\begin{matrix} {u u}_{n no d d}^{* *} \\ {u u}_{n no q q}^{* *} \end{matrix}] = = \frac{22}{33} [\begin{matrix} {cosθ cosθ}_{n no} & c c o o s the s (({θ θ}_{n no} - - \frac{22 π π}{33})) & c c o o s the s (({θ θ}_{n no} + + \frac{22 π π}{33})) \\ - - {sinθ sinθ}_{n no} & - - sin sin (({θ θ}_{n no} - - \frac{22 π π}{33})) & - - s the s i i n no (({θ θ}_{n no} + + \frac{22 π π}{33})) \end{matrix}] [\begin{matrix} {u u}_{n no a a}^{* *} \\ {u u}_{n no b b}^{* *} \\ {u u}_{n no c c}^{* *} \end{matrix}];;$

式中：分别为的d轴、q轴分量。In the formula: respectively d-axis, q-axis components.

4.4将步骤4.3得到的三相可控逆变器的网侧电压指令和网侧电压矢量u_ndq的差值Δu_ndq送入电压环比例积分-谐振(PI-R)控制器，得到三相可控逆变器的控制电压v_cdq；其中，比例积分-谐振(PI-R)控制器在s域下的传递函数为：4.4 The grid-side voltage command of the three-phase controllable inverter obtained in step 4.3 The difference Δu _ndq with the grid-side voltage vector u _ndq is sent to the voltage loop proportional-integral-resonant (PI-R) controller to obtain the control voltage v _cdq of the three-phase controllable inverter; among them, the proportional-integral-resonant (PI-R -R) The transfer function of the controller in the s domain is:

${G G}_{R R} ((s the s)) = = {K K}_{p p} + + \frac{{K K}_{i i}}{s the s} + + \frac{{K K}_{r r} s the s}{{s the s}^{22} + + 22 {ω ω}_{c c} s the s + + {((66 {ω ω}_{g g}))}^{22}};;$

式中：K_p、K_i、K_r分别为PI-R控制器的比例系数、积分系数和谐振系数；ω_c为谐振控制器的截止频率，用以增加谐振控制器的响应带宽，降低其对谐振点频率波动的敏感程度；In the formula: K _p , K _i , K _r are the proportional coefficient, integral coefficient and resonance coefficient of the PI-R controller respectively; ω _c is the cut-off frequency of the resonance controller, which is used to increase the response bandwidth of the resonance controller and reduce its Sensitivity to frequency fluctuations at the resonance point;

4.5参照步骤3.5，利用步骤4.2得到的输出电压位置角θ_n将步骤4.4得到的三相可控逆变器的控制电压v_cdq作Park反变换，获得静止坐标系下三相可控逆变器的调制电压u_cαβ；4.5 Referring to step 3.5, use the output voltage position angle θ _n obtained in step 4.2 to perform Park inverse transformation on the control voltage v _cdq of the three-phase controllable inverter obtained in step 4.4, and obtain the three-phase controllable inverter in the static coordinate system The modulation voltage u _cαβ ;

4.6参照步骤3.6，将步骤4.5得到的三相可控逆变器的调制电压u_cαβ送入空间矢量调制(SVM)模块，即可产生三相可控逆变器的开关信号s₁、s₂、s₃，实现对三相可控逆变器的预期控制。4.6 Referring to step 3.6, send the modulation voltage u _cαβ of the three-phase controllable inverter obtained in step 4.5 into the space vector modulation (SVM) module, and then the switching signals s ₁ and s ₂ of the three-phase controllable inverter can be generated , s ₃ , to achieve the expected control of the three-phase controllable inverter.

上述步骤1～4共同构成了本发明的柴储型军用交流移动电站的电能质量控制方法。The above steps 1-4 jointly constitute the power quality control method of the diesel storage type military AC mobile power station of the present invention.

与现有技术相比，本发明具有的有益效果是：Compared with prior art, the beneficial effect that the present invention has is:

1)采用锂电池、超级电容和双向DC-DC变换器组成的复合储能装置，能够有效缓冲脉冲或阶跃功率负荷对电网的冲击，且能够实现对锂电池充放电电流的精确控制，延长了设备的使用寿命；1) The composite energy storage device composed of lithium battery, supercapacitor and bidirectional DC-DC converter can effectively buffer the impact of pulse or step power load on the power grid, and can realize precise control of lithium battery charging and discharging current, extending the The service life of the equipment;

2)Boost模式下，双向DC-DC变换器的控制增加了一个直流母线电压幅值判断环节(或滞环控制)，允许母线电压在一定范围内波动，该设计既发挥了超级电容的高功率密度特性，又降低了锂电池充放电的频率；2) In Boost mode, a DC bus voltage amplitude judgment link (or hysteresis control) is added to the control of the bidirectional DC-DC converter, allowing the bus voltage to fluctuate within a certain range. This design not only exerts the high power of the super capacitor Density characteristics, and reduce the frequency of lithium battery charge and discharge;

3)通过对三相可控逆变器控制方法的改进，实现了对电网谐波污染的主动治理，提高了军用交流移动电站的电能输出质量。3) Through the improvement of the control method of the three-phase controllable inverter, the active control of the harmonic pollution of the power grid is realized, and the power output quality of the military AC mobile power station is improved.

附图说明Description of drawings

图1为本发明的柴储型军用交流移动电站的拓扑结构及信号采集图；Fig. 1 is the topological structure and the signal acquisition diagram of the diesel storage type military AC mobile power station of the present invention;

图2为本发明的柴储型军用交流移动电站的双向DC-DC变换器电路结构图；Fig. 2 is the bidirectional DC-DC converter circuit structure diagram of diesel storage type military AC mobile power station of the present invention;

图3为本发明的柴储型军用交流移动电站的双向DC-DC变换器控制原理图；Fig. 3 is the control schematic diagram of the bidirectional DC-DC converter of the diesel storage type military AC mobile power station of the present invention;

图4为本发明的柴储型军用交流移动电站的三相可控整流器控制原理图；Fig. 4 is the control schematic diagram of the three-phase controllable rectifier of the diesel storage type military AC mobile power station of the present invention;

图5为本发明的柴储型军用交流移动电站的三相可控逆变器控制原理图；Fig. 5 is the control schematic diagram of the three-phase controllable inverter of the diesel storage type military AC mobile power station of the present invention;

图6为本发明的柴储型军用交流移动电站接入脉冲功率负载时的仿真运行结果；Fig. 6 is the simulated operation result when the diesel storage type military AC mobile power station of the present invention is connected to a pulse power load;

图7为本发明的柴储型军用交流移动电站接入非线性负载时的仿真运行结果；Fig. 7 is the simulated operation result when the diesel storage type military AC mobile power station of the present invention is connected to a nonlinear load;

图中，柴油发电机组1、锂电池2、超级电容3、三相可控整流器4、双向DC-DC变换器5和三相可控逆变器6。In the figure, a diesel generator set 1, a lithium battery 2, a supercapacitor 3, a three-phase controllable rectifier 4, a bidirectional DC-DC converter 5 and a three-phase controllable inverter 6.

具体实施方式detailed description

下面结合附图和实施案例对本发明作进一步说明。The present invention will be further described below in conjunction with accompanying drawings and examples of implementation.

图1为本发明的柴储型军用交流移动电站拓扑结构及信号采集图。本发明所描述的一种柴储型军用交流移动电站主要包括以下组成部件：柴油发电机组1、锂电池2、超级电容3、三相可控整流器4、双向DC-DC变换器5和三相可控逆变器6；其中，锂电池2、超级电容3和双向DC-DC变换器5共同构成本发明的复合储能装置。上述各组成部件集成于一个军用标准方舱之内，且各部件之间具有如下电气连接关系：Fig. 1 is the topological structure and signal acquisition diagram of the diesel storage type military AC mobile power station of the present invention. A diesel storage type military AC mobile power station described in the present invention mainly includes the following components: diesel generator set 1, lithium battery 2, super capacitor 3, three-phase controllable rectifier 4, bidirectional DC-DC converter 5 and three-phase A controllable inverter 6; wherein, the lithium battery 2, the supercapacitor 3 and the bidirectional DC-DC converter 5 jointly constitute the composite energy storage device of the present invention. The above-mentioned components are integrated in a military standard shelter, and the electrical connections between the components are as follows:

柴油发电机组1的三相交流电输出端，连接到三相可控整流器4的输入端，三相可控整流器4的输出端并联到直流母线上；锂电池2的输出端，连接到双向DC-DC变换器5的输入端(低压端)，双向DC-DC变换器5的输出端(高压端)并联到直流母线上；超级电容3直接并联到直流母线上；三相可控逆变器6的输入端连接到直流母线上，三相可控逆变器6的输出端连接到用电设备(负载)。The three-phase AC output terminal of the diesel generator set 1 is connected to the input terminal of the three-phase controllable rectifier 4, and the output terminal of the three-phase controllable rectifier 4 is connected to the DC bus in parallel; the output terminal of the lithium battery 2 is connected to the bidirectional DC- The input terminal (low voltage terminal) of the DC converter 5 and the output terminal (high voltage terminal) of the bidirectional DC-DC converter 5 are connected in parallel to the DC bus; the supercapacitor 3 is directly connected in parallel to the DC bus; the three-phase controllable inverter 6 The input end of the three-phase controllable inverter 6 is connected to the DC bus, and the output end of the three-phase controllable inverter 6 is connected to the electrical equipment (load).

如图1所示，本发明所描述的一种柴储型军用交流移动电站及其电能质量控制方法，需利用传感器采集的信号有：柴油发电机组输出的机侧三相交流电压U_gabc和机侧三相交流电流I_gabc，锂电池的输出电流(或锂电池的放电电流)I_dc，直流母线电压U_dc，三相可控逆变器输出的网侧三相交流电压u_nabc，直流侧负载电流I_load。As shown in Figure 1, in the diesel storage type military AC mobile power station and its power quality control method described in the present invention, the signals that need to be collected by sensors include: the three-phase AC voltage U gabc on the machine side output by the diesel generator set and the machine-side three-phase AC voltage U _gabc side three-phase AC current I _gabc , lithium battery output current (or lithium battery discharge current) I _dc , DC bus voltage U _dc , grid-side three-phase AC voltage u _nabc output by the three-phase controllable inverter, and DC side The load current I _load .

图2为本发明的柴储型军用交流移动电站的双向DC-DC变换器电路结构图，图中：T₁和T₂为功率管(这里定义T₁为上功率管、T₂为下功率管)；L₁为储能电感，起到蓄流作用；C₁和C₂为支撑电容(这里定义C₁为高压端支撑电容、C₂为低压端支撑电容)，起到稳定电压的作用。双向DC-DC变换器工作时，上、下两个功率管T₁和T₂不能同时开通，锂电池放电模式(Boost模式)下，下功率管T₂动作，上功率管T₁的驱动信号闭锁，锂电池利用上功率管T₁的反并联二极管D₁续流向母线传递能量，储能电感L₁的存在确保了电流的连续输出，且可以通过控制T₂的开通占空比，对L₁上流过的电流进行控制；锂电池充电模式(Buck模式)下，上功率管T₁动作，下功率管T₂可靠封锁，利用下功率管T₂的反并联二极管D₂续流向锂电池回馈能量(充电)，且同样可以通过控制T₁的开通占空比，对L₁上流过的电流进行控制。Fig. 2 is the bidirectional DC-DC converter circuit structure diagram of diesel storage type military AC mobile power station of the present invention, among the figure: T ₁ and T ₂ are power tubes (definition T ₁ here is upper power tube, T ₂ is lower power tube); L ₁ is the energy storage inductor, which plays the role of current storage; C ₁ and C ₂ are supporting capacitors (here, C ₁ is defined as the high-voltage end supporting capacitor, and C ₂ is the low-voltage end supporting capacitor), which plays the role of stabilizing the voltage . When the bidirectional DC-DC converter is working, the upper and lower power transistors T1 and T2 cannot be turned _on at the same time. _In the lithium battery discharge mode (Boost mode), the lower power transistor T2 _operates , and the driving signal _of the upper power transistor T1 Latching, the lithium battery uses the anti-parallel diode D ₁ of the upper power transistor T ₁ to transfer energy to the bus bar. The existence of the energy storage inductor L ₁ ensures the continuous output of the current, and can control the on-duty ratio of T ₂ to control the L ₁ is controlled by the current flowing through the top; in lithium battery charging mode (Buck mode), the upper power tube T ₁ operates, the lower power tube T ₂ is reliably blocked, and the anti-parallel diode D ₂ of the lower power tube T ₂ is used to continue to feed back to the lithium battery Energy (charging), and the current flowing through L1 can also be controlled by controlling the _on _- duty cycle of T1.

图3为本发明的柴储型军用交流移动电站的双向DC-DC变换器控制原理图；双向DC-DC变换器的作用是控制锂电池的电能充放，维持母线电压的稳定。如图3所示，双向DC-DC变换器的控制方法为：Fig. 3 is the control schematic diagram of the bidirectional DC-DC converter of the diesel storage type military AC mobile power station of the present invention; the function of the bidirectional DC-DC converter is to control the charging and discharging of lithium batteries and maintain the stability of the bus voltage. As shown in Figure 3, the control method of the bidirectional DC-DC converter is:

1.锂电池Boost模式、Buck模式的切换受控于模式选择开关ST₁的输入项，即锂电池的荷电状态Soc，具体为：当Soc大于设定阈值Soc_min时，双向DC-DC变换器切换至Boost模式；反之，当Soc小于等于设定阈值Soc_min时，双向DC-DC变换器切换至Buck模式；1. The switching between Boost mode and Buck mode of the lithium battery is controlled by the input item of the mode selection switch ST ₁ , that is, the state of charge Soc of the lithium battery, specifically: when the Soc is greater than the set threshold Soc _min , the bidirectional DC-DC conversion The converter switches to Boost mode; conversely, when Soc is less than or equal to the set threshold Soc _min , the bidirectional DC-DC converter switches to Buck mode;

对于一般的磷酸铁锂电池，Soc_min可设定为40％。For general lithium iron phosphate batteries, Soc _min can be set to 40%.

2.Boost模式下，当直流母线电压U_dc的幅值低于设定阈值电压U_dcmin时，直流母线电压指令与直流母线电压U_dc的差值ΔU_dc送入电压环比例积分(PI)控制器，得到下功率管调制电压U_d，将下功率管调制电压U_d送入PWM模块，即可产生下功率管T₂的触发信号S_d；反之直流母线电压U_dc的幅值高于等于设定阈值电压U_dcmin时，下功率管T₂的触发信号S_d设置为零；该模式下，上功率管T₁的触发信号始终设置为零，即上功率管T₁处于闭锁状态；2. In Boost mode, when the amplitude of the DC bus voltage U _dc is lower than the set threshold voltage U _dcmin , the DC bus voltage command The difference ΔU _dc from the DC bus voltage U _dc is sent to the voltage loop proportional integral (PI) controller to obtain the modulation voltage U _{d of the lower power tube, and the modulation voltage U d} _of the lower power tube is sent to the PWM module to generate the lower power _The trigger signal S _d of tube T2 _; otherwise, when the amplitude of the DC bus voltage U _dc is higher than or equal to the set threshold voltage U _dcmin , the trigger signal S _d of the lower power tube T2 is set to zero; in this mode, the upper power tube _The trigger signal of T1 is always set to zero, that is, the upper power transistor T1 is in _a locked state;

该模式下，下功率管T₂的触发信号设置需同步考虑直流母线电压幅值的原因是：充分发挥超级电容的瞬时功率输出特性，允许母线电压有一定范围的波动，且只有当直流母线电压低到一定程度(阈值电压U_dcmin)时，锂电池才开始放电，快速维持母线电压稳定，该设置能够在一定程度上减少锂电池放电的次数，从而延长锂电池的使用寿命。 _In this mode, the trigger signal setting of the lower power transistor T2 needs to consider the amplitude of the DC bus voltage synchronously because: the instantaneous power output characteristics of the supercapacitor are fully utilized, and the bus voltage is allowed to fluctuate within a certain range, and only when the DC bus voltage The lithium battery starts to discharge when it is low to a certain level (threshold voltage U _dcmin ), and quickly maintains the bus voltage stability. This setting can reduce the number of lithium battery discharges to a certain extent, thereby prolonging the service life of the lithium battery.

3.Buck模式下，锂电池的电流指令与锂电池的输出电流ΔI_dc的差值送入电流环比例积分(PI)控制器，得到上功率管调制电压U′_d；将上功率管调制电压U′_d送入与步骤2相同的PWM模块，即可产生上功率管T₁的触发信号S′_d；该模式下，下功率管T₂的触发信号始终为零，即下功率管T₂处于闭锁状态；3. In Buck mode, the current command of the lithium battery The difference with the output current ΔI _dc of the lithium battery is sent to the current loop proportional-integral (PI) controller to obtain the upper power tube modulation voltage _U'd ; the upper power tube modulation voltage _U'd is sent to the same PWM as step 2 Module can generate the trigger signal _S'd of the upper power tube T1 _; in this mode, the trigger signal of the lower power tube _T2 is always zero, that is, the lower power tube T2 is in a locked state _;

图4为本发明的柴储型军用交流移动电站三相可控整流器的控制原理图；三相可控整流器的作用是将柴油发电机组的输出电压由交流转换成直流，其控制采用基于空间矢量调制的直接功率控制方法。如图4所示，三相可控整流器的控制方法具体为：Fig. 4 is the control schematic diagram of the three-phase controllable rectifier of the diesel storage type military AC mobile power station of the present invention; Modulated direct power control method. As shown in Figure 4, the control method of the three-phase controllable rectifier is as follows:

4.柴油发电机组输出的机侧三相交流电压U_gabc首先送入传统的数字锁相环PLL进行锁相，获得机侧三相交流电压的位置角θ_g、角频率ω_g和幅值U_g；4. The generator-side three-phase AC voltage U _gabc output by the diesel generator set is first sent to the traditional digital phase-locked loop PLL for phase-locking, and the position angle θ _g , angular frequency ω _g and amplitude U of the generator-side three-phase AC voltage are obtained _g ;

5.柴油发电机组输出的机侧三相交流电压U_gabc、机侧三相交流电流I_gabc送入功率计算模块，得到柴油发电机组的输出有功功率P_g、输出无功功率Q_g；5. The generator-side three-phase AC voltage U _gabc and the generator-side three-phase AC current I _gabc output by the diesel generator set are sent to the power calculation module to obtain the output active power P _g and output reactive power Q _g of the diesel generator set;

功率计算方程为：The power calculation equation is:

$\{\begin{matrix} {P P}_{g g} = = {U u}_{g g a a} \cdot &Center Dot; {I I}_{g g a a} + + {U u}_{g g b b} \cdot &Center Dot; {I I}_{g g b b} + + {U u}_{g g c c} \cdot &Center Dot; {I I}_{g g c c} \\ {Q Q}_{g g} = = 11 / / \sqrt{33} (((({U u}_{g g b b} - - {U u}_{g g c c})) \cdot &Center Dot; {I I}_{g g a a})) + + (({U u}_{g g c c} - - {U u}_{g g a a})) \cdot &Center Dot; {I I}_{g g b b} + + (({U u}_{g g a a} - - {U u}_{g g b b})) \cdot \cdot {I I}_{g g c c})) \end{matrix} - - - - - - ((11))$

式中：U_ga、U_gb、U_gc分别为U_gabc的A相、B相、C相分量；I_ga、I_gb、I_gc分别为I_gabc的A相、B相、C相分量。In the formula: U _ga , U _gb , and U _gc are the A-phase, B-phase, and C-phase components of U _gabc , respectively; I _ga , I _gb , and I _gc are the A-phase, B-phase, and C-phase components of I _gabc , respectively.

6.柴油发电机组的有功功率指令无功功率指令分别与其对应的输出有功功率P_g、输出无功功率Q_g作差，其差值ΔP_g、ΔQ_g分别送入功率环比例积分(PI)控制器，得到三相可控整流器的有功电压指令V_gd和无功电压指令V_gq；其中，柴油发电机组的有功功率指令无功功率指令计算方程为：6. Active power command of diesel generator set reactive power command Make difference with the corresponding output active power P _g and output reactive power Q _g respectively, and the difference ΔP _g and ΔQ _g are respectively sent to the power loop proportional-integral (PI) controller to obtain the active voltage command of the three-phase controllable rectifier V _gd and reactive voltage command V _gq ; among them, the active power command of diesel generator set reactive power command The calculation equation is:

$\{\begin{matrix} {P P}_{g g}^{* *} = = {U u}_{d d c c} \cdot &Center Dot; {I I}_{l l o o a a d d} \\ {Q Q}_{g g}^{* *} = = 00 \end{matrix} - - - - - - ((22))$

本步骤中PI控制器的调节过程，可以表示为：The adjustment process of the PI controller in this step can be expressed as:

$\{\begin{matrix} {V V}_{g g d d} = = (({k k}_{g g p p} + + \frac{{k k}_{g g i i}}{s the s})) (({P P}_{g g}^{* *} - - {P P}_{g g})) \\ {V V}_{g g q q} = = (({k k}_{g g p p} + + \frac{{k k}_{g g i i}}{s the s})) (({Q Q}_{g g}^{* *} - - {Q Q}_{g g})) \end{matrix} - - - - - - ((33))$

式中：k_gp、k_gi分别为功率环PI控制器的比例系数和积分系数。In the formula: k _gp and k _gi are the proportional coefficient and integral coefficient of the power loop PI controller respectively.

7.步骤6得到三相可控整流器的有功电压指令V_gd、无功电压指令V_gq分别加上各自的补偿项，得到三相可控整流器的有功控制电压U_cd、无功控制电压U_cq；具体计算方程为：7. In step 6, the active voltage command V _gd and the reactive voltage command V _gq of the three-phase controllable rectifier are respectively added with respective compensation items to obtain the active control voltage U _cd and reactive control voltage U _cq of the three-phase controllable rectifier ; The specific calculation equation is:

$\{\begin{matrix} {U u}_{c c d d} = = - - {V V}_{g g d d} + + (({U u}_{g g} - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {Q Q}_{g g})) \\ {U u}_{c c q q} = = {V V}_{g g q q} - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {P P}_{g g} \end{matrix} - - - - - - ((44))$

式(4)为三相可控整流器采用直接功率控制时的控制电压表达式，其推导过程介绍如下：Equation (4) is the control voltage expression when the three-phase controllable rectifier adopts direct power control, and its derivation process is introduced as follows:

正转同步速旋转坐标系下，三相可控整流器的瞬时功率可以表示为：In the forward synchronous speed rotating coordinate system, the instantaneous power of the three-phase controllable rectifier can be expressed as:

$\begin{matrix} {P P}_{g g} + + {jQ jQ}_{g g} = = \frac{33}{22} {U u}_{g g d d q q} \cdot \cdot {\overset{^^}{I I}}_{g g d d q q} \\ = = \frac{33}{22} \frac{{U u}_{g g}}{{L L}_{g g}} (({\overset{^^}{ψ ψ}}_{g g d d q q} - - {\overset{^^}{ψ ψ}}_{c c d d q q})) \end{matrix} - - - - - - ((55))$

式中：U_gdq为正转同步速旋转坐标系下三相可控整流器的输入电压矢量，亦即柴油发电机组的输出电压矢量；为正转同步速旋转坐标系下三相可控整流器的输入电流矢量I_gdq(亦即柴油发电机组的输出电流矢量)的共轭矢量；为三相可控整流器的输入磁链矢量ψ_gdq的共轭矢量；为三相可控整流器的控制磁链矢量ψ_cdq的共轭矢量。In the formula: U _gdq is the input voltage vector of the three-phase controllable rectifier in the forward rotation synchronous speed rotating coordinate system, that is, the output voltage vector of the diesel generator set; is the conjugate vector of the input current vector _Igdq (that is, the output current vector of the diesel generator set) of the three-phase controllable rectifier under the forward synchronous speed rotating coordinate system; is the conjugate vector of the input flux vector ψ _gdq of the three-phase controllable rectifier; It is the conjugate vector of the control flux linkage vector ψ _cdq of the three-phase controllable rectifier.

当采用d轴电网电压定向时，有：When using the d-axis grid voltage orientation, there are:

$\{\begin{matrix} {U u}_{g g d d} = = - - {ω ω}_{g g} {ψ ψ}_{g g q q} = = {U u}_{g g} \\ {U u}_{g g q q} = = {ω ω}_{g g} {ψ ψ}_{g g d d} = = 00 \end{matrix} - - - - - - ((66))$

式中：U_gd、U_gq分别为U_gdq的d轴、q轴分量；ψ_gd、ψ_gq分别为ψ_gdq的d轴、q轴分量。In the formula: U _gd , U _gq are the d-axis and q-axis components of U _gdq respectively; ψ _gd , ψ _gq are the d-axis and q-axis components of ψ _gdq respectively.

将式(6)带入式(5)，并写成标量形式，可得：Put formula (6) into formula (5) and write it in scalar form, we can get:

$\{\begin{matrix} {P P}_{g g} = = - - \frac{33}{22} \frac{{U u}_{g g}}{{L L}_{g g}} {ψ ψ}_{c c d d} \\ {Q Q}_{g g} = = \frac{33}{22} \frac{{U u}_{g g}}{{L L}_{g g}} (({ψ ψ}_{c c q q} + + \frac{{U u}_{g g}}{{ω ω}_{g g}})) \end{matrix} - - - - - - ((77))$

式中：ψ_cd、ψ_cq分别为ψ_cdq的d轴、q轴分量。In the formula: ψ _cd , ψ _cq are the d-axis and q-axis components of ψ _cdq respectively.

对式(7)等号两边分别取微分运算，可得：Taking differential operations on both sides of the equal sign in formula (7), we can get:

$\{\begin{matrix} \frac{{dψ dψ}_{c c d d}}{d d t t} = = - - \frac{22}{33} \frac{{L L}_{g g}}{{U u}_{g g}} \frac{{dP dP}_{g g}}{d d t t} = = - - \frac{22}{33} \frac{{L L}_{g g}}{{U u}_{g g}} \frac{{P P}_{g g}^{* *} - - {P P}_{g g}}{{T T}_{s the s}} \\ \frac{{dψ dψ}_{c c q q}}{d d t t} = = \frac{22}{33} \frac{{L L}_{g g}}{{U u}_{g g}} \frac{{dQ wxya}_{g g}}{d d t t} = = \frac{22}{33} \frac{{L L}_{g g}}{{U u}_{g g}} \frac{{Q Q}_{g g}^{* *} - - {Q Q}_{g g}}{{T T}_{s the s}} \end{matrix} - - - - - - ((88))$

式中：T_s为系统采样周期。正转同步速旋转坐标系下，三相可控整流器的电压方程可表示为：Where: T _s is the system sampling period. In the forward synchronous speed rotating coordinate system, the voltage equation of the three-phase controllable rectifier can be expressed as:

U_cdq＝dψ_cdq/dt+jω_gψ_cdq(9)U _cdq = dψ _cdq /dt+jω _g ψ _cdq (9)

式中：U_cdq为三相可控整流器的控制电压矢量。Where: U _cdq is the control voltage vector of the three-phase controllable rectifier.

将式(7)、(8)带入式(9)，可得：Put formulas (7), (8) into formula (9), we can get:

$\{\begin{matrix} {U u}_{c c d d} = = - - \frac{22}{33} \frac{{L L}_{g g}}{{U u}_{g g} {T T}_{s the s}} (({P P}_{g g}^{* *} - - {P P}_{g g})) - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {Q Q}_{g g} + + {U u}_{g g} \\ {U u}_{c c q q} = = \frac{22}{33} \frac{{L L}_{g g}}{{U u}_{g g} {T T}_{s the s}} (({Q Q}_{g g}^{* *} - - {Q Q}_{g g})) - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {P P}_{g g} \end{matrix} - - - - - - ((1010))$

这样，当采用比例积分(PI)控制器对有功、无功功率进行调节时，式(10)可以重新表达为：In this way, when a proportional-integral (PI) controller is used to regulate active and reactive power, equation (10) can be re-expressed as:

$\begin{matrix} \{\begin{matrix} {U u}_{c c d d} = = - - (({k k}_{g g p p} + + \frac{{k k}_{g g i i}}{s the s})) (({P P}_{g g}^{* *} - - {P P}_{g g})) - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {Q Q}_{g g} + + {U u}_{g g} \\ {U u}_{c c q q} = = (({k k}_{g g p p} + + \frac{{k k}_{g g i i}}{s the s})) (({Q Q}_{g g}^{* *} - - {Q Q}_{g g})) - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {P P}_{g g} \end{matrix} - - - - - - ((1111)) \\ \{\begin{matrix} {U u}_{c c d d} = = - - \frac{22}{33} \frac{{L L}_{g g}}{{U u}_{g g} {T T}_{s the s}} (({P P}_{g g}^{* *} - - {P P}_{g g})) - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {Q Q}_{g g} + + {U u}_{g g} \\ {U u}_{c c q q} = = \frac{22}{33} \frac{{L L}_{g g}}{{U u}_{g g} {T T}_{s the s}} (({Q Q}_{g g}^{* *} - - {Q Q}_{g g})) - - \frac{22}{33} \frac{{ω ω}_{g g} {L L}_{g g}}{{U u}_{g g}} {P P}_{g g} \end{matrix} - - - - - - ((1010)) \end{matrix}$

进一步，将(3)带入式(11)，即可得式(4)。证毕。Further, bring (3) into formula (11) to get formula (4). Certificate completed.

8.利用步骤7获得的机侧三相交流电压的位置角θ_g对步骤7得到的有功控制电压U_cd、无功控制电压U_cq进行Park反变换，得到静止坐标系下的有功调节电压U_cα、无功调节电压U_cβ；8. Use the position angle θ _g of the machine-side three-phase AC voltage obtained in step 7 to perform Park inverse transformation on the active control voltage U _cd and reactive control voltage U _cq obtained in step 7, and obtain the active power regulation voltage U in the stationary coordinate system _cα , reactive power regulation voltage U _cβ ;

$[\begin{matrix} {U u}_{c c α α} \\ {U u}_{c c β β} \end{matrix}] = = [\begin{matrix} {cosθ cosθ}_{g g} & {sinθ sinθ}_{g g} \\ - - {sinθ sinθ}_{g g} & {cosθ cosθ}_{g g} \end{matrix}] [\begin{matrix} {U u}_{c c d d} \\ {U u}_{c c q q} \end{matrix}] - - - - - - ((1212))$

9.将步骤8得到的静止坐标系下的有功调节电压U_cα、无功调节电压U_cβ进行空间矢量调制(SVM)，即可获得三相可控整流器的开关信号s_a、s_b、s_c，实现对三相可控整流器的有效控制。9. Perform space vector modulation (SVM) on the active power regulation voltage U _cα and reactive power regulation voltage U _cβ in the static coordinate system obtained in step 8, and then the switching signals s _a , s _b , s of the three-phase controllable rectifier can be obtained _c , realize the effective control of the three-phase controllable rectifier.

图4为本发明的柴储型军用交流移动电站三相可控逆变器的控制原理图；三相可控逆变器的作用是将直流电转换为负载所需的三相交流电，并对电网谐波污染进行治理。参照图4，三相可控逆变器的控制方法为：Fig. 4 is the control schematic diagram of the three-phase controllable inverter of diesel storage type military AC mobile power station of the present invention; Harmonic pollution is controlled. Referring to Figure 4, the control method of the three-phase controllable inverter is:

10.生成三相可控逆变器的三相电压指令具体为：10. Generate the three-phase voltage command of the three-phase controllable inverter Specifically:

$\{\begin{matrix} {u u}_{n no a a}^{* *} = = M m \cdot \cdot s the s i i n no (({ω ω}_{g g} \cdot &Center Dot; t t + + {ω ω}_{00})) \\ {u u}_{n no b b}^{* *} = = M m \cdot &Center Dot; s the s i i n no (({ω ω}_{g g} \cdot &Center Dot; t t + + {ω ω}_{00} - - 22 π π / / 33)) \\ {u u}_{n no c c}^{* *} = = M m \cdot &Center Dot; s the s i i n no (({ω ω}_{g g} \cdot \cdot t t + + {ω ω}_{00} + + 22 π π / / 33)) \end{matrix} - - - - - - ((1313))$

11.参照步骤4，将步骤10生成的三相电压指令送入传统的数字锁相环PLL，得到三相可控逆变器的输出电压位置角θ_n；11. Referring to step 4, the three-phase voltage command generated in step 10 Send it into the traditional digital phase-locked loop PLL to get the output voltage position angle θ _n of the three-phase controllable inverter;

12.利用步骤11得到的输出电压位置角θ_n分别对三相电压指令和网侧三相交流电压u_nabc进行Park变换，得到三相可控逆变器的网侧电压指令和网侧电压矢量u_ndq；12. Use the output voltage position angle θ _n obtained in step 11 to set the three-phase voltage command Perform Park transformation with the grid-side three-phase AC voltage u _nabc to obtain the grid-side voltage command of the three-phase controllable inverter and grid-side voltage vector u _ndq ;

$[\begin{matrix} {u u}_{n no d d}^{* *} \\ {u u}_{n no q q}^{* *} \end{matrix}] = = [\begin{matrix} {cosθ cosθ}_{n no} & cos cos (({θ θ}_{n no} - - \frac{22 π π}{33})) & cos cos (({θ θ}_{n no} + + \frac{22 π π}{33})) \\ - - {sinθ sinθ}_{n no} & - - sin sin (({θ θ}_{n no} - - \frac{22 π π}{33})) & - - sin sin (({θ θ}_{n no} + + \frac{22 π π}{33})) \end{matrix}] [\begin{matrix} {u u}_{n no a a}^{* *} \\ {u u}_{n no b b}^{* *} \\ {u u}_{n no c c}^{* *} \end{matrix}] - - - - - - ((1414))$

13.将步骤12得到的三相可控逆变器的网侧电压指令和网侧电压矢量u_ndq的差值Δu_ndq送入电压环比例积分-谐振(PI-R)控制器，得到三相可控逆变器的控制电压v_cdq；其中，比例积分-谐振(PI-R)控制器在s域下的传递函数为：13. The grid-side voltage command of the three-phase controllable inverter obtained in step 12 The difference Δu _ndq with the grid-side voltage vector u _ndq is sent to the voltage loop proportional-integral-resonant (PI-R) controller to obtain the control voltage v _cdq of the three-phase controllable inverter; among them, the proportional-integral-resonant (PI-R -R) The transfer function of the controller in the s domain is:

${G G}_{R R} ((s the s)) = = {K K}_{p p} + + \frac{{K K}_{i i}}{s the s} + + \frac{{K K}_{r r} s the s}{{s the s}^{22} + + 22 {ω ω}_{c c} s the s + + {((66 {ω ω}_{g g}))}^{22}} - - - - - - ((1515))$

式中：K_p、K_i、K_r分别为PI-R控制器的比例系数、积分系数和谐振系数；ω_c为谐振控制器的截止频率，主要用于增加谐振控制器的响应带宽，降低其对谐振点频率波动的敏感程度。In the formula: K _p , K _i , K _r are the proportional coefficient, integral coefficient and resonance coefficient of the PI-R controller respectively; _ωc is the cut-off frequency of the resonance controller, which is mainly used to increase the response bandwidth of the resonance controller and reduce the Its sensitivity to frequency fluctuations at the resonance point.

这里，采用PI-R取代传统的PI控制器的原因是：军用负载设备中多含有大量的5次、7次谐波，如不加以治理，必将引起三相可控逆变器输出电压的畸变，进而影响其他敏感用电设备的运行安全。值得关注的是，5次、7次谐波在正转同步速旋转坐标系下表现为6倍电网频率(6ω_g)的负序、正序交流分量。而传统的PI控制器只能实现对直流分量的无静差调节，对频率为6ω_g的交流分量则无能为力。谐振控制器则具有较好的正、负序双向谐振特性，可以专门用于调节高频交流分量。故此，本发明中电压控制器选用PI-R控制器，以此弥补PI控制器在高频部分的幅值衰减缺陷，进而实现对电压基频分量、谐波分量的统一和快速调节。Here, the reason for using PI-R to replace the traditional PI controller is that military load equipment contains a large number of 5th and 7th harmonics. If they are not treated, it will inevitably cause the output voltage of the three-phase controllable inverter to drop. Distortion, which in turn affects the operation safety of other sensitive electrical equipment. It is worth noting that the 5th and 7th harmonics appear as negative-sequence and positive-sequence AC components of 6 times the grid frequency (6ω _g ) in the forward synchronous speed rotating coordinate system. However, the traditional PI controller can only realize the adjustment of the DC component without static error, but it is powerless to the AC component with a frequency of 6ω _g . The resonance controller has better positive and negative sequence bidirectional resonance characteristics, and can be specially used to adjust high-frequency AC components. Therefore, the voltage controller in the present invention uses a PI-R controller to make up for the amplitude attenuation defect of the PI controller in the high frequency part, and then realize the unified and rapid adjustment of the fundamental frequency component and harmonic component of the voltage.

14.参照步骤8，利用步骤11得到的输出电压位置角θ_n对步骤13得到的三相可控逆变器的控制电压v_cdq作Park反变换，获得静止坐标系下三相可控逆变器的调制电压u_cαβ；14. Referring to step 8, use the output voltage position angle θ _n obtained in step 11 to perform inverse Park transformation on the control voltage v _cdq of the three-phase controllable inverter obtained in step 13 to obtain a three-phase controllable inverter in the static coordinate system The modulation voltage u _cαβ of the device;

15.参照步骤9，将步骤14得到的三相可控逆变器的调制电压u_cαβ送入空间矢量调制(SVM)模块，即可产生三相可控逆变器的开关信号s₁、s₂、s₃，实现对三相可控逆变器的预期控制。15. Referring to step 9, send the modulation voltage u _cαβ of the three-phase controllable inverter obtained in step 14 to the space vector modulation (SVM) module, and then the switching signals s ₁ and s of the three-phase controllable inverter can be generated ₂ , s ₃ , realize the expected control of the three-phase controllable inverter.

上述步骤1～15共同构成了本发明的柴储型军用交流移动电站的电能质量控制方法。The above steps 1-15 jointly constitute the power quality control method of the diesel storage type military AC mobile power station of the present invention.

图6为本发明的柴储型军用交流移动电站接入脉冲功率负载时的仿真运行结果；图中i_nabc为逆变变流器输出的网侧三相交流电流，其他符号含义同图1。从图6可以看出，本发明所述的柴储型军用交流移动电站具有较强的动态带载能力，体现在：1)脉冲负荷的投切并未引起逆变变流器输出的网侧三相交流电压u_nabc波形的振荡或畸变；2)脉冲负载投入时，复合储能装置首先输出瞬时电能(见I_dc波形，类似一个尖峰形式)，确保母线电压的稳定(见U_dc波形，上下波动2V左右)，之后由柴油发电机组输出负载所需的平均功率(见I_gabc波形)，该结构设计增强了军用交流电站抗击外部脉冲负载扰动的能力。Fig. 6 is the simulation operation result when the diesel-storage type military AC mobile power station of the present invention is connected to a pulse power load; in the figure, _inabc is the grid-side three-phase AC current output by the inverter converter, and the meanings of other symbols are the same as those in Fig. 1. It can be seen from Fig. 6 that the diesel-storage type military AC mobile power station of the present invention has a strong dynamic load capacity, which is reflected in: 1) The switching of pulse loads does not cause the grid side of the inverter converter output Oscillation or distortion of the three-phase AC voltage u _nabc waveform; 2) When the pulse load is put in, the composite energy storage device first outputs instantaneous electric energy (see I _dc waveform, similar to a peak form) to ensure the stability of the bus voltage (see U _dc waveform, fluctuate up and down about 2V), and then the average power required by the load is output by the diesel generator set (see _Igabc waveform). This structural design enhances the ability of the military AC power station to resist external pulse load disturbances.

图7为本发明的柴储型军用交流移动电站接入非线性负载时的仿真运行结果。为了展示本发明的柴储型军用交流移动电站的电能质量控制方法的优越性，仿真分两个阶段进行：1)阶段I(0.1～0.2s)，逆变变流器的电压控制器采用传统的PI控制器，无电网污染治理控制；2)阶段II(0.2～0.3s)，逆变变流器的电压控制器采用本发明的PI-R控制器，有电网污染治理控制。对比图7中逆变变流器输出的网侧三相交流电压u_nabc和网侧三相交流电流i_nabc的波形可知，传统PI控制下，电压、电流波形中含有丰富的5次、7次谐波，严重威胁电网中其他并联敏感用电设备的运行安全；采用本发明的控制策略后，电网谐波污染得到了有效治理，经过傅立叶分析计算，网侧三相交流电压的总谐波失真度(THD)由阶段I的9.36％降到阶段II的3.6％。Fig. 7 is the simulation operation result when the diesel storage type military AC mobile power station of the present invention is connected to a nonlinear load. In order to demonstrate the superiority of the power quality control method of the diesel storage type military AC mobile power station of the present invention, the simulation is carried out in two stages: 1) Stage I (0.1～0.2s), the voltage controller of the inverter converter adopts the traditional PI controller without power grid pollution control; 2) Phase II (0.2-0.3s), the voltage controller of the inverter converter adopts the PI-R controller of the present invention, with power grid pollution control. Comparing the waveforms of grid-side three-phase AC voltage u _nabc and grid-side three-phase AC current i _nabc output by the inverter converter in Figure 7, we can see that under traditional PI control, the voltage and current waveforms contain rich 5th and 7th order Harmonics seriously threaten the operation safety of other parallel sensitive electrical equipment in the power grid; after adopting the control strategy of the present invention, the harmonic pollution of the power grid has been effectively controlled. After Fourier analysis and calculation, the total harmonic distortion of the three-phase AC voltage on the grid side Degree (THD) dropped from 9.36% in Phase I to 3.6% in Phase II.

综上，本发明所述一种柴储型军用交流移动电站及其电能质量控制方法，可以有效平抑脉冲功率负载引起的直流母线电压波动，且能够有效抑制负载端引入的电压谐波，提高输出电能质量，从而确保敏感用电负载的安全可靠运行。复合储能装置的存在一方面使得柴油发电机组的容量大幅降低，另一方面由于结合了锂电池高能量密度、超级电容高功率密度的优点，有效控制了锂电池的充放电次数和外部电磁冲击，延长了设备的使用寿命。In summary, the diesel storage type military AC mobile power station and its power quality control method described in the present invention can effectively stabilize the DC bus voltage fluctuations caused by pulse power loads, effectively suppress the voltage harmonics introduced by the load end, and improve the output Power quality, so as to ensure the safe and reliable operation of sensitive electric loads. On the one hand, the existence of the composite energy storage device greatly reduces the capacity of the diesel generator set. On the other hand, due to the combination of the high energy density of the lithium battery and the high power density of the super capacitor, the charging and discharging times of the lithium battery and the external electromagnetic shock are effectively controlled. , prolong the service life of the equipment.

Claims

1. the military interchange mobile power station of bavin storage type, it is characterized in that, described bavin storage type military interchange mobile power station mainly comprises following building block: the controlled inverter of diesel generating set, lithium battery, super capacitor, three-phase controlled rectifier, bidirectional DC-DC converter and three-phase; Above-mentioned each component integration is within a military standard shelter, and between each parts, there is following electric connecting relation: the three-phase alternating current output of diesel generating set is connected to the input of three-phase controlled rectifier, and the output of three-phase controlled rectifier is parallel on DC bus; The output of lithium battery is connected to the low-pressure end of bidirectional DC-DC converter, and the high-pressure side of bidirectional DC-DC converter is parallel on DC bus; Super capacitor is directly parallel on DC bus; The input of the controlled inverter of three-phase is connected on DC bus, and the output of the controlled inverter of three-phase is connected to power consumption equipment.

2. an electric energy quality control method for the military interchange mobile power station of bavin storage type according to claim 1, is characterized in that, mainly comprise the following steps:

A1. transducer is utilized to gather following signal: the pusher side three-phase alternating voltage U that diesel generating set exports _gabcwith pusher side three-phase alternating current I _gabc, output current (or discharging current) I of lithium battery _dc, DC bus-bar voltage U _dc, the net side three-phase alternating voltage u that the controlled inverter of three-phase exports _nabc, DC side load current I _load;

A2. according to the state-of-charge Soc of lithium battery, the control model of bidirectional DC-DC converter is divided into Boost pattern and Buck pattern, is specially:

A2.1. when the state-of-charge Soc of lithium battery is greater than setting threshold Soc _mintime, bidirectional DC-DC converter switches to Boost pattern; Otherwise, when Soc is less than or equal to setting threshold Soc _mintime, bidirectional DC-DC converter switches to Buck pattern;

A2.2. under Boost pattern, as DC bus-bar voltage U _dcamplitude lower than set threshold voltage U _dcmintime, by DC bus-bar voltage instruction with DC bus-bar voltage U _dcdifference DELTA U _dcsend into Voltage loop pi controller, obtain lower power tube modulation voltage U _d; By lower power tube modulation voltage U _dsend into PWM module, the lower power tube T of bidirectional DC-DC converter can be produced ₂triggering signal S _d; Otherwise DC bus-bar voltage U _dcamplitude be more than or equal to set threshold voltage U _dcmintime, lower power tube T ₂triggering signal S _dbe set to zero; Under Boost pattern, the upper power tube T of bidirectional DC-DC converter ₁triggering signal be set to zero all the time, namely go up power tube T ₁be in blocking;

A2.3. under Buck pattern, by the current-order of lithium battery with the output current I of lithium battery _dcdifference DELTA I _dcsend into electric current loop pi controller, obtain power tube modulation voltage U ' _d; By upper power tube modulation voltage U ' _dsend into the PWM module identical with steps A 2.2, power tube T can be produced ₁triggering signal S ' _d; Under Buck pattern, lower power tube T ₂triggering signal be always zero, namely descend power tube T ₂be in blocking;

A3. three-phase controlled rectifier adopts the improvement direct Power Control method based on space vector modulation, is specially:

A3.1. the pusher side three-phase alternating voltage U of diesel generating set output _gabcfirst sending into traditional digital phase-locked loop PLL carries out phase-locked, obtains the angular position theta of pusher side three-phase alternating voltage _g, angular frequency _gwith amplitude U _g;

A3.2. the pusher side three-phase alternating voltage U of diesel generating set output _gabc, pusher side three-phase alternating current I _gabcsend into power computation module, obtain the active power of output P of diesel generating set _g, output reactive power Q _g;

A3.3. the active power instruction of diesel generating set reactive power instruction active power of output P corresponding with it respectively _g, output reactive power Q _gdiffer from, its difference DELTA P _g, Δ Q _gsend into power ring pi controller respectively, obtain the active voltage instruction V of three-phase controlled rectifier _gdwith reactive voltage instruction V _gq; Wherein, the active power instruction of diesel generating set reactive power instruction accounting equation is:

\{\begin{matrix} P_{g}^{*} = U_{d c} \cdot I_{l o a d} \\ Q_{g}^{*} = 0 \end{matrix};

The active voltage instruction V of the three-phase controlled rectifier A3.4. steps A 3.3 obtained _gd, reactive voltage instruction V _gqadd respective compensation term respectively, obtain the real power control voltage U of three-phase controlled rectifier _cd, idle control voltage U _cq; Concrete accounting equation is:

\{\begin{matrix} U_{c d} = - V_{g d} + (U_{g} - \frac{2}{3} \frac{ω_{g} L_{g}}{U_{g}} Q_{g}) \\ U_{c q} = V_{g q} - \frac{2}{3} \frac{ω_{g} L_{g}}{U_{g}} P_{g} \end{matrix};

In formula: L _gfor the filter inductance of three-phase controlled rectifier;

The angular position theta of the pusher side three-phase alternating voltage A3.5. utilizing steps A 3.1 to obtain _gto the real power control voltage U that steps A 3.4 obtains _cd, idle control voltage U _cqcarry out Park inverse transformation, obtain the meritorious regulation voltage U under rest frame _{c α}, Reactive-power control voltage U _{c β};

A3.6. the meritorious regulation voltage U under rest frame steps A 3.5 obtained _{c α}, Reactive-power control voltage U _{c β}carry out space vector modulation, the switching signal s of three-phase controlled rectifier can be obtained _a, s _b, s _c, realize the effective control to three-phase controlled rectifier;

A4. direct current is converted to the three-phase alternating current needed for load by the controlled inverter of three-phase, and administers harmonic pollution in electric power net, and its control method is:

A4.1. the three-phase voltage instruction of the controlled inverter of three-phase is generated be specially:

\{\begin{matrix} u_{n a}^{*} = M \cdot s i n (ω_{g} \times t + ω_{0}) \\ u_{n b}^{*} = M \cdot s i n (ω_{g} \times t + ω_{0} - 2 π / 3) \\ u_{n c}^{*} = M \cdot s i n (ω_{g} \times t + ω_{0} + 2 π / 3) \end{matrix};

In formula: M is the amplitude of phase voltage, and has ω ₀for the starting phase angle of three-phase voltage, be set to zero; be respectively three-phase voltage instruction a phase, B phase, C phase component;

A4.2. with reference to steps A 3.1, the three-phase voltage instruction that steps A 4.1 is generated send into traditional digital phase-locked loop PLL, obtain the output voltage angular position theta of the controlled inverter of three-phase _n;

A4.3. the output voltage angular position theta that steps A 4.2 obtains is utilized _n, respectively to three-phase voltage instruction with net side three-phase alternating voltage u _nabccarry out Park conversion, obtain the voltage on line side instruction of the controlled inverter of three-phase with voltage on line side vector u _ndq;

The voltage on line side instruction of the controlled inverter of three-phase A4.4. steps A 4.3 obtained with voltage on line side vector u _ndqdifference DELTA u _ndqsend into Voltage loop proportional integral-resonant controller, obtain the control voltage v of the controlled inverter of three-phase _cdq; Wherein, the transfer function of proportional integral-resonance (PI-R) controller under s territory is:

G_{R} (s) = K_{p} + \frac{K_{i}}{s} + \frac{K_{r} s}{s^{2} + 2 ω_{c} s + {(6 ω_{g})}^{2}};

In formula: K _p, K _i, K _rbe respectively the proportionality coefficient of proportional integral-resonant controller, integral coefficient and resonance coefficient; ω _cfor the cut-off frequency of resonant controller;

A4.5. with reference to steps A 3.5, the output voltage angular position theta that steps A 4.2 obtains is utilized _nthe control voltage v of the controlled inverter of three-phase that steps A 4.4 is obtained _cdqmake Park inverse transformation, the modulation voltage u of the controlled inverter of three-phase under acquisition rest frame _{c α β};

A4.6. with reference to steps A 3.6, the modulation voltage u of the controlled inverter of three-phase that steps A 4.5 is obtained _{c α β}send into space vector modulation module, the switching signal s of the controlled inverter of three-phase can be produced ₁, s ₂, s ₃, realize controlling the expection of the controlled inverter of three-phase.