CN1046419A - Control arrangement for inverter current - Google Patents

Control arrangement for inverter current Download PDF

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Publication number
CN1046419A
CN1046419A CN90101119A CN90101119A CN1046419A CN 1046419 A CN1046419 A CN 1046419A CN 90101119 A CN90101119 A CN 90101119A CN 90101119 A CN90101119 A CN 90101119A CN 1046419 A CN1046419 A CN 1046419A
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China
Prior art keywords
current
deviation
instruction
pwm
motor
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CN1017766B (en
Inventor
水野公元
平林辉美
高桥达司
村松洋
多和田正典
小寺利幸
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Publication of CN1046419A publication Critical patent/CN1046419A/en
Publication of CN1017766B publication Critical patent/CN1017766B/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
  • Inverter Devices (AREA)

Abstract

Control arrangement for inverter current of the present invention, be provided with the arithmetic unit of operand word current command value, current instruction value is transformed to the DA converting means of analog current instruction, thereby the difference of instruction of power taking stream and motor current is tried to achieve the deviation device of analog current deviation, the amplifying device of simulation amplified current deviation, to be transformed into the AD converter of digital value through the amplified current deviation, the data generating device that the voltage instruction of the PWM speed that will match with digital value is exported as time data, and inverter is generated digital PWM circuit with the corresponding pulse signal of switching signal according to time data.

Description

Control arrangement for inverter current
The present invention relates to the control arrangement for inverter current of control of induction or synchronous motor rotating speed and torque etc., particularly cheapness and the high control arrangement for inverter current of control precision.
Fig. 5 for put down in writing on the 92nd page～94 pages and the 209th page～210 pages of expression for example goes up a hill that a straight man of virtue and ability edit, July nineteen eighty-two, NEC academy issued " novel drive electronics " books, with the block diagram of the control arrangement for inverter current that has earlier of vector control.Herein, be by three-phase voltage U, V and W institute induction motor driven as an example motor (6), there is shown the threephase motor electric current I U that supplies with motor (6) with sinusoidal waveform control *, IV *And IW *Situation.
Among the figure, good based on three-phase input voltage R, S and T(with single-phase reference power supply), to the main circuit of motor (6) output three-phase voltage U, V and W by the diode bridge (1) that input voltage R, S and T is carried out rectification, make diode bridge (1) both end voltage become the filtering capacitor (2) of direct voltage and this direct voltage is carried out the inverter (3) that pulse-width modulation (PWM) is transformed into three-phase voltage U, V and W to be constituted.Inverter (3) then is made of the switching device that constitutes electric bridge (for example, transistor, FET, IGBT, GTO etc.), has just formed PWM control to three-phase voltage U, V and W because each of each phase is alternately carried out open and close controlling to switching device.
At this moment, the filter action that relies on motor (6) self to have is pressed sinusoidal waveform to three-phase voltage U, V and W, or the motor current IU of three-phase *, IV *And IW *Controlled.
At the U of inverter (3) mutually and V the phase output terminal current transformer (4) and (5) that are provided with respectively, detection U phase and V motor current IU mutually *And IV *, simultaneously, the pulse signal generator (7) that is made of encoder etc. detects the rotational speed omega r of motor (6) *The speed command ω r that (8) output of speed command generating unit and target velocity or target torque are suitable.
Subtracter (9) is obtained rotational speed omega r *The output speed deviation △ ω r(=ω r-ω r with the difference of speed command ω r *), velocity-variation amplifier (10) amplifies this velocity deviation △ ω r, output and the proportional torque current instruction of the output torque of motor (6) i gThis torque current instruction i qThe excitation current instruction i of respective settings with the specification of pressing motor (6) dTogether, be input to current amplitude calculating part (11), phase angle calculating portion (12) and revolutional slip calculating part (13).
Current amplitude calculating part (11) is tried to achieve current amplitude instruction (I) by following formula:
〔Ⅰ〕＝（id 2+iq 2） 1/2
This phase angle instruction θ i constantly tries to achieve from following formula in phase calculation portion (12):
θi＝tan -1（i q/id）
Revolutional slip calculating part (13) is tried to achieve revolutional slip frequencies omega s from following formula:
ωs＝（L 6/R 6）（i q/id）
＝（L 6/R 6）tanθi
But, L 6And R 6The inductance and the resistance of expression motor (6) are motor constants.Adder (14) is obtained revolutional slip frequencies omega s and rotational speed omega r *And, output rotary electromagnetic field frequency instruction ω (=ω r *+ ω s), phase counter (15) carries out the rotatable phase instruction θ r that time integral output is represented with following formula to frequency instruction ω:
θr＝∫（ωr ＊+ωs）dt
Adder (16) obtains rotatable phase instruction θ r and phase angle instruction θ i sum, the final θ of bit instruction mutually (=θ r+ θ i) of output.
Current-order generating unit (17) is instructed current amplitude | I | and multiply each other with bit instruction mutually, try to achieve three-phase current command value Iu, Iv and Iw from following formula with digital depths:
Iu＝|Ⅰ|·sinθ
Iv＝|Ⅰ|·sin（θ-2π/3）
Iw＝|Ⅰ|·sin（θ+2π/3）
Current-order Iu, the Iv and the Iw that further are transformed into simulation are input to electric current enlarging section (18).But as described later and since the command value mutually relevant with W can U mutually and the command value of V phase calculate, so in fact be input to the current-order of electric current enlarging section (18) as long as U phase and V current-order Iu and Iv mutually.
The motor current Iu that electric current enlarging section (18) will be obtained from current transformer (4) and (5) actual detected of current-order Iu and Iv *And Iv *Between difference amplify, try to achieve the current deviation △ I (△ Iu, △ Iv and △ Iw) of each phase from following formula:
△Iu＝Iu-Iu ＊
△Iv＝Iv-Iv ＊
△Iw＝-（△Iu+△Iv）
Be input to PWM portion (19).
PWM portion (19) generates switching signal C according to current deviation △ I to inverter (3).That is, connect the switching device that cuts off in the inverter (3), terminal voltage U, V and the W of control motor (6), thereby the speed (or torque) of control motor (6) for making current deviation △ I become zero.
Then, under the occasion of the current-order generating unit (17) in by general analog current control circuit in the pie graph 5, electric current enlarging section (18) and PWM portion (19), one side simultaneously is illustrated with reference to Fig. 6～Fig. 8.
Among Fig. 6, current-order generating unit (17) is by the microcomputer of purchasing CPU, RAM and ROM (20), DA converter (21) and (22) formation.
Microcomputer (20) carries out above-mentioned digital current command value Iu that obtains and the calculating of Iv, and DA converter (21) and (22) will be transformed into the analogue value from the result of calculation of microcomputer (20), as current-order Iu and Iv output.
Electric current enlarging section (18) is made of subtracter (23) and (24), adder (25) and analog current amplifier (26)～(28).Current-order Iu and Iv and motor current Iu are obtained in subtracter (23) and (24) *And Iv *Between poor, simultaneously, analog current amplifier (26) and (27) are amplified from the difference signal of subtracter (23) and (24) and as current deviation △ Iu and △ Iv and are exported.Adder (25) power taking stream deviation △ Iu and △ Iv sum, analog current amplifier (28) with negative polarity amplify from adder (25) and signal, and it is exported as current deviation △ Iw.
The comparator (30) that PWM portion (19) is provided with respectively by carrier-frequency oscilaltor (29), each phase place, prevent that short circuit current (31) and base amplifier (32) from constituting.The carrier signal F(of carrier-frequency oscilaltor (29) output certain frequency and triangular waveform is with reference to Fig. 7), comparator 30 to each carrier signal of each phase place F and current deviation △ I by simulating comparison mutually, with comparative result as pulse signal Co(Cou, Cov and Cow) output.Switching signal C under " H " level of this pulse signal Co and the switching device of connecting in the inverter (3) during branch road 2Corresponding, " L " level is the switching signal C when connecting branch road on it then 1Corresponding.
But, as everyone knows,,, therefore, as shown in Figure 8, make down branch road switching signal C because the short circuit of branch road up and down will take place the transient of switching device if allow switching signal C use pulse signal Co same as before 2With last branch road switching signal C 1Each rising sequential only postpone to prevent duration of short circuit Td.Further, base amplifier (32) is with each switching signal C 1And C 2After being amplified to set level, output and each corresponding switching signal C(Cu of branch road about each mutually 1, Cu 2, Cv 1, Cv 2, Cw 1And Cw 2), and be added on the interior switching device of inverter (3).
More than be an example that constitutes electric current enlarging section (18) and PWM portion (19) with the analog current control circuit, then, just the occasion that constitutes with the full digital current control circuit simultaneously with reference to Fig. 9～Figure 12, simultaneously is illustrated.
Among Fig. 9, microcomputer (40) is in the function that comprises electric current enlarging section (18), and interior harness has high-resolution AD converter (41).It also is feasible on the microcomputer 40 that AD converter (41) is connected to as external equipment.
Microcomputer (40) is reading in the motor current Iu that is transformed into digital value with AD converter (41) *And Iv *The time, instructing from current amplitude as hereinbefore | I| calculates current-order Iu and Iv with bit instruction θ mutually, obtains current-order Iu and Iv and motor current Iu *And Iv *Between difference and amplified, try to achieve suitable digital value with current deviation △ I.Then, generate voltage instruction Vu, Vv and the Vw of the PWM frequency that matches with current deviation △ I with map table, and with these as each data Dt of each time mutually 1And Dt 2Be input to pwm circuit (42).
Figure 10 is the block diagram of expression with timer IC formation digital PWM circuit (42) one examples, two timer IC(43) and (44), for example, the microcomputer external timer LS I8253 series that the market that available Intel Company makes can be buied constitutes.Figure 10 only illustrates a phase wherein, in fact, is provided with and each corresponding three groups of same timer IC(43) and (44).
The function that has carrier-frequency oscilaltor (29) and the comparator (30) of Fig. 6 on digital PWM circuit (42) principle is with three-phase pulse signal Co(Cou, Cov and Cow) output to and prevent short circuit current (31).Herein, as Figure 11 and shown in Figure 7, determine uniquely from the triangular waveform edge of carrier signal F to the time t of switching pulse signal Co according to the value of current deviation △ I 1And t 2Therefore, use voltage instruction Vu, Vv and the Vw of the PWM frequency that offsets with current deviation △ I value to generate, with from carrier pulse CF(with reference to Figure 11) begin to rise to the suitable time t of decline of pulse signal Co 1, and the time t suitable with the pulse duration of pulse signal Co 2Suitable time data Dt 1And Dt 2If be entered into each the timer IC(43 in the digital PWM circuit (42)) and (44), desired pulse signal Co will be obtained.
That is timer IC(43) according to data Dt 1And Dt 2And carrier pulse CF output pulse width t 1Data pulse Ct 1, simultaneously, timer IC(44) along with data pulse Ct 1Rising and when moving, according to time data Dt 1And Dt 2Output pulse width t 2Pulse signal Co.
Figure 12 is the block diagram of another example of expression full digital device, and in this case, speed command generating unit functions such as (8) all is included in the one chip microcomputer (40A).The details of this mode, for example, use department's will, No. 2,107 volumes in the civilian Chi D(industry of Japanese T electricity mood association's opinion) " " the high performance control method of big capacity induction motor " (with reference to the 159th～166 page, special the 161st page Fig. 2) of (in February, 1987 electric association distribution) done record.
Among the figure, sine and cosine generating unit (45) generates sinusoidal signal sin θ and cosine signal cos θ according to frequency instruction ω.The coordinate conversion portion (46) of input side is according to the actual motor current Iu through digital conversion *And Iv *And sinusoidal signal sin θ and cosine signal cos θ, the isolated actual torque current i of output direct current q *With exciting current id.Adder (47) obtains torque current instruction iq and torque current iq *Between poor, output torque current deviation △ iq(=iq-iq *), adder (48) obtains excitation current instruction id and exciting current id *Between poor, output exciting current deviation △ id (=id-id *).
On the one hand, the coordinate conversion portion (49) of outlet side is according to torque current deviation △ iq and exciting current deviation △ id and sinusoidal signal sin θ and cosine signal cos θ, generates voltage in three phases instruction Vu, Vv and Vw, and with them as time data Dt 1And Dt 2Output to digital PWM circuit (42).Also have, the details of coordinate conversion portion (46) and (49), for example, going up a hill that a straight man of virtue and ability edits, doing record on the 210th page of Figure 64 2 of document " novel drive electronics " of July nineteen eighty-two, the distribution of Japanese electric mood academy, as may be obvious that from the document, very miscellaneous calculation has been carried out in coordinate conversion portion (46) and (49).
The control arrangement for inverter current that has earlier has analog and Fig. 9 and full digital illustrated in fig. 12 illustrated in fig. 6 as mentioned above.
Yet, under analog situation, for obtaining current-order Iu, Iv and Iw, DA converter (21) and (22) that high speed motion two passages must be arranged, simultaneously, for obtaining pulse signal Co, because carrier-frequency oscilaltor (29) and comparator (30) must be arranged, just there is the problem that can't realize miniaturization and so in institute so that hardware becomes big.And, owing to be difficult to the gain of change and the corresponding analog current amplifier of electromotor velocity (26) and (27), so analog current amplifier (26) and (27) are difficult to carry out bias correction adjustment and error correction etc., the result, existence is the problem of Current Control accurately.
On the one hand, the occasion of full digital is because the resolution of AD converter (41) is low and current pulsation increases, for preventing these, so must adopt the high-resolution AD converter (41) of 12 grades of high price.And, because microcomputer (40) or (40A) in the calculation process content become very complicated, be prevention because the Current Control sampling postpones the unsteadiness that produces, so must adopt the high speed and the microcomputer at high price of Digital Signal Processing for example etc.Therefore, just has the problem analog variety of issue, high this class of relevant cost that solves.
So the purpose of this invention is to provide the control arrangement for inverter current that can address the above problem, this device because to possess strong points analog and the full digital both sides inexpensive and control precision is high.
Control arrangement for inverter current of the present invention, be provided with: the arithmetic unit of the current instruction value of computing numeral, current instruction value is transformed to the DA converting means of the current-order of simulation, thereby the difference that obtains current-order and motor current is tried to achieve the deviation device of analog current deviation, the amplifying device of simulation amplified current deviation, to be transformed to the AD converter of digital value through the amplified current deviation, the data generating device that the voltage instruction of the PWM speed that will match with digital value is exported as time data, and inverter is generated digital PWM circuit with the corresponding pulse signal of switching signal according to time data.
In the present invention, current instruction value is transformed to the current-order of the basic sine of simulation with the DA converting means, try to achieve the current-order of simulation and the current deviation between the motor current with deviation device and amplifying device, inexpensive AD converter with low resolution is delivered to microcomputer with this current deviation, is generated as production burst signal time necessary data accurately according to the digital processing in the microcomputer.
Fig. 1 is the functional-block diagram of the major part of expression one embodiment of the invention,
Fig. 2 is the flow chart of the action of microcomputer in the presentation graphs 1,
Fig. 3 is used for the PWM device of key diagram 1 and the oscillogram of low pass filter action,
Fig. 4 is used for the subtracter of key diagram 1 and the oscillogram of analog current amplifier action,
Fig. 5 is the block diagram of the control arrangement for inverter current that has earlier of expression,
Fig. 6 is the block diagram of expression with the example of the current-order generating unit among the Fig. 5 that analog current control circuit was constituted that has earlier, current amplifier portion and PWM part,
Fig. 7 is used for the oscillogram that key diagram 6 PWM partly move,
Fig. 8 is used for the oscillogram that key diagram 6 short circuits prevent the action of circuit,
Fig. 9 is for representing with the block diagram of full digital current control circuit formation with an example of the current-order generating unit among Fig. 5, current amplifier portion and PWM portion.
Figure 10 is the block diagram of digital PWM circuit structure in the presentation graphs 9,
Figure 11 is the oscillogram that is used to illustrate the action of Figure 10,
Figure 12 is the block diagram of expression with the function of another example of microcomputer of the full digital device that has earlier.
Label is described as follows in each accompanying drawing:
(3) ... inverter (6) ... motor
(23), (24) ... subtracter (deviation device)
(26), (27) ... analog current amplifier (amplifying device)
(42) ... the digital PWM circuit
(50) ... microprocessor (51) ... arithmetic unit
(52), (53) ... PWM device (DA converting means)
(54) ... AD converter (55) ... data generating device
(56) ... low pass filter (DA switch)
Iu, Iv ... current instruction value Iu, Iv ... current-order
Pu, Pv ... the pwm pulse sequence
Iu *, Iv *Motor current
△ Iu, △ Iv ... electronic deviation
Vu, Vv, Vw ... voltage instruction
Dt 1, Dt 2Time data
Co ... pulse signal, C ... switching signal
Moreover same label is represented same or suitable part among the figure.
Below referring to figs. 1 through Fig. 4 one embodiment of the invention are illustrated.
Fig. 1 is the block diagram of the major function of explanation one embodiment of the invention, the deviation device is subtracter (23) and (24), and amplifying device be analog current amplifier (26) with (27) with illustrated in fig. 6 identical, digital PWM circuit (42) is with illustrated in fig. 9 identical.Also have, unshowned structure is exactly according to Fig. 5 and illustrated in fig. 9 such in Fig. 1.
The flow chart of the sequence of movement of microcomputer in Fig. 2 presentation graphs 1 (50),
Fig. 3 is used for the PWM device (52) of key diagram 1 and the oscillogram of (53) and low pass filter (56) action,
Fig. 4 is the oscillogram of the action of the subtracter (23) that is used for key diagram 1 and (24) and analog current amplifier (26) and (27).
Microcomputer (50) has itself: the AD converter (54) of two PWM devices (52) of calculate the arithmetic unit of current instruction value Iu and Iv, being made up of the sawtooth waveforms pwm circuit and (53), 8 hyte low resolution and contain promising digital value current deviation △ I and be transformed into time data Dt 1And Dt 2The data generating device of map table, the output in PWM device (52) and (53) all is connected to low pass filter (56).PWM device (52) and (53) and low pass filter (56) constitute the DA converting means, and its function is equivalent to DA converter (21) and (22) among Fig. 6.
At first, arithmetic unit (51) instructs according to current amplitude | I| and bit instruction θ mutually, with similarly aforementioned, from following formula try to achieve U mutually and V current instruction value Iu and Iv(mutually go on foot S1):
Iu＝｜I｜·sinθ
Iv＝｜I｜·sin（θ-2π/3）
The Iu and the Iv that obtain are input to PWM device (52) and (53) (step S2) respectively.
The PWM device (52) of U phase side, as shown in Figure 3, with the sawtooth waveforms Fp of certain frequency and current instruction value Iu(with reference to dotted line) compare, generate the pwm pulse sequence Pu of the PWM speed that matches with current instruction value Iu.Similarly, the PWM device (53) of V phase side, the pwm pulse sequence Pv of the PWM speed that generation and current instruction value Iv match.Low pass filter (56) is removed the carrier frequency composition of sawtooth waveforms Fp contained in pwm pulse sequence Pu and Pv, is transformed into the current-order Iu and the Iv that are made up of the fundamental sine wave of simulation.
At this moment, if getting 8, the carrier frequency of sawtooth waveforms Fp, the resolution of PWM device (52) and (53) gets 20KH 2, because the frequency of utilization conversion is 1600rpm(60H to the maximum usually 2), then current-order Iu and the Iv by low pass filter (56) becomes the extraordinary complete sinusoidal waveform of response.
The subtracter (23) that constitutes the deviation device is obtained current-order Iu and motor current Iu from current transformer (4) *(with reference to Fig. 4 dotted line) poor, analog current amplifier (26) amplifies the difference signal from subtracter (23), and as shown in Figure 4, output is as the waveform suitable with phase difference of current deviation △ Iu.Similarly, subtracter (24) obtain current-order Iv with from the motor current Iv of current transformer (5) *Between poor, by analog current amplifier (27) output current deviation △ Iv.
Resulting like this current deviation △ Iu and Iv are transformed into digital value with AD converter (54), deliver to microcomputer (50) (step S3) again.At this moment, because the current deviation voltage of input AD converter (54) only is positive voltage, do not need the level off normal.In addition, motor (6) motor current Iu when not powering up *And Iv *Current deviation △ Iu and △ Iv when being zero are input to microcomputer (50) in advance, if, then carrying out the temperature drift of analog current amplifier (26) and (27) automatically and accurately as the zero reference level, current deviation value that will be at this moment proofreaies and correct, adjusts discrete correction etc.Further, owing to use the analog circuit of forming by subtracter (23), (24) analog current amplifier (26) and (27) with amplified current deviation △ Iu and △ Iv, be input to AD converter (54), so even the low also complete very high precision that obtains out of question of words of the resolution of AD converter (54).
Data generating device (55) in the microcomputer (50) contains the arithmetic section of the current deviation △ Iw of computing W phase, with similarly aforementioned, can try to achieve the current deviation △ Iw(step S4 of W phase from following formula):
△Iw＝-（△Iu+△Iv）
Then, according to the map table in the data generating device (55), as time data Dt 1And Dt 2Generate three-phase voltage instruction Vu, the Vv and the Vw of the PWM speed that matches with each current deviation △ Iu, △ Iv and △ Iw respectively, these signals are input to digital PWM circuit (42) (step S5).
Below, with similarly aforementioned, digital PWM circuit (42) generates and the corresponding three-phase pulse signal of switching signal C Co(Cou, Cov and Cow inverter (3)), by preventing the switching device in short circuit current (31), base amplifier (32) the open and close controlling inverter (3).
Like this, rely on the combination of analog and full digital and constitute the hybrid circuit mode, promptly use the AD converter (54) of the cheapness of low resolution also can obtain very high precision.In addition, constitute the DA converting means that the current-order sine wave takes place if adopt cheap PWM device (52), (53) and low pass filter (56), just do not need DA converter (21) and (22) shown in Figure 6, thus more inexpensive.Further, calculate current instruction value with the arithmetic unit (51) in the microcomputer (50), the current deviation with the calculating of the data generating device (55) in the microcomputer (50) W phase not only can finely carry out calculation process, and owing to handle simply, so the processing time is also short.
Also have, in the above-described embodiments, PWM device (52), (53) and AD converter (54) all are that microcomputer (50) itself carries, even but to be connected to microcomputer (50) as external equipment also be feasible.
Equally, take to fetch current amplitude instruction by microcomputer (50) | I| and the way of bit instruction θ mutually, even but the speed command generating unit (8) among Fig. 5～adder (16) all is contained within the microcomputer (50) also is feasible.
In addition, though digital PWM circuit (42) and microcomputer (50) are provided with respectively, as timer (43) and (44) of Figure 10 are also constituted with monolithic form with microcomputer (50), much less can further reduce component count.
Such the present invention is provided with as mentioned above: the computing device of the current instruction value of computing numeral, current instruction value is transformed into the DA converting means of the current-order of simulation, obtaining current instruction and differing from of motor current and the deviation device of the current deviation that obtains simulating, amplifying device with current deviation simulation amplification, the current deviation that has amplified is transformed into the AD converter of the low resolution of numeral value, the data generating device that the voltage instruction of the PWM speed that will match with current deviation is exported as the time data, and the digital PWM circuit that inverter is generated the pulse signal corresponding with the conversion signal according to the time data, because digital operation partly is formed in the single chip microcomputer, has the effect that can receive the high control arrangement for inverter current of cheap control precision.
Shown in Figure 1
23,24: subtracter (deviation device)
26,27: analog current amplifier (amplifying device)
Iu, Iv: current instruction value
Pu, the Pv:PWM train of pulse
Iu, Iv: current-order
Iu ＊，Iv ＊: motor current
△ Iu, △ Iv: current deviation
Vu, Vv, Vw: voltage instruction
Dt 1，Dt 2: the time data
Co: pulse signal

Claims (1)

1, inverter switch device is carried out PWM control, thereby a kind of control arrangement for inverter current of the alternating current of motor is supplied with in control, it is characterized in that comprising:
The arithmetic unit that the current instruction value of described motor numeral is carried out computing,
Described current instruction value is transformed into the DA converting means of the current-order of simulation,
Thereby get the deviation device that differs from the current deviation of trying to achieve simulation between the motor current of described current-order and the described motor of effective supply,
Described current deviation is simulated the amplifying device of amplification,
To be transformed into the AD converter of digital value through the described current deviation of amplification,
The data generating device that the voltage instruction of the PWM speed that described and digital value are matched is exported as time data, and
According to described time data and to the digital PWM circuit of described inverter generation with the corresponding pulse signal of switching signal.
CN90101119A 1989-04-10 1990-02-28 Control arrangement for inverter current Expired CN1017766B (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP88035/89 1989-04-10
JP1088035A JP2653873B2 (en) 1989-04-10 1989-04-10 Inverter current controller

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Publication Number Publication Date
CN1046419A true CN1046419A (en) 1990-10-24
CN1017766B CN1017766B (en) 1992-08-05

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Publication number Priority date Publication date Assignee Title
JP4664836B2 (en) * 2006-02-28 2011-04-06 オリジン電気株式会社 Three-phase voltage type AC / DC converter
JP6874517B2 (en) * 2017-05-12 2021-05-19 株式会社デンソー Motor control device that performs vector control of synchronous motors

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JPS6059831B2 (en) * 1980-06-23 1985-12-26 三菱電機株式会社 Polyphase inverter output voltage control device
JPS6279380A (en) * 1985-10-01 1987-04-11 Meidensha Electric Mfg Co Ltd Constant measurement of induction motor
JPS6288787A (en) * 1985-10-14 1987-04-23 三菱電機株式会社 Controller for alternating current elevator
JPS63171192A (en) * 1987-01-09 1988-07-14 Hitachi Ltd Controller for elevator

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JPH02269495A (en) 1990-11-02
CN1017766B (en) 1992-08-05
JP2653873B2 (en) 1997-09-17
KR900017267A (en) 1990-11-15

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