CN104639220A - Signal receiving and transmitting device and method adopting smart antenna - Google Patents

Abstract

The embodiment of the invention provides a signal receiving and transmitting device and method adopting a smart antenna. The signal receiving and transmitting device comprises an antenna array, a client spatial correlation matrix unit, a weight vector solution unit, a broadcast beam forming switching unit, a service beam forming switching unit and a weighting network forming unit, wherein the antenna array comprises N antenna units; each antenna unit is connected with M weighters; the client spatial correlation matrix unit is used for determining a formed weighting network having M*N weighters; the weight vector solution unit is connected with the client spatial correlation matrix unit, and is used for computing a weighting network weight matrix based on the weighting network, and computing the weight vector of a client according to the weighting network weight matrix; in the broadcast beam forming switching unit, a high-gain dual-polarized antenna is adopted, and the weight value of the high-gain dual-polarized antenna is set; in the service beam forming switching unit, a transposed matrix of the weight vector is multiplied with a switching matrix to obtain a service beam weight vector; and in the weighting network forming unit, broadcast beam forming is implemented in a broadcast beam time slot based on the weight value of the high-gain dual-polarized antenna, and service beam forming is implemented in a service time slot based on a service beam weight vector.

Description

A kind of signal receiving/transmission device and method adopting smart antenna

Technical field

The present invention relates to mobile communication technology, refer to a kind of signal receiving/transmission device and the method that adopt smart antenna especially.

Background technology

Along with popularizing of mobile communication, frequency spectrum becomes more and more valuable resource.At existing time division multiple access (TDMA, Time Division Multiple Access), frequency division multiple access (FDMA, Frequency Division Multiple Access) or code division multiple access (CDMA, Code Division Multiple Access) on multiplex mode basis, smart antenna (SA, Smart Antenna) technology introduces fourth dimension multiple access multiplexing mode-space division multiple access (SDMA, Space Division Multiple Access), make user at identical time slot, in same frequency or identical address code situation, still can distinguish according to its spatial propagation path, thus extend the capacity of mobile communication system exponentially.

Smart antenna original name adaptive antenna array (AAA, Adaptive Antenna Array), is applied to radar, sonar and military aspect at first, mainly completes space filtering and location, and phased array radar is a kind of better simply adaptive antenna array.Along with the development of mobile communication and the research to aspects such as mobile communication radio wave propagation, networking technology, antenna theories, the disposal ability of digital signal chip improves constantly, and adaptive antenna array starts the mobile communication for having complicated radio propagation environment.

Smart antenna is as one of the key technology of TD-SCDMA, and its application level directly determines the quality of TD network quality.Smart antenna is a kind of multi-antenna-unit system in essence, can by excitation (also claiming the weights)-amplitude of each antenna element of adjustment and phase place, antenna beam pattern shape is made to become specified beams shape, realize wave beam forming, wave beam forming is divided into: business beam shaping, broadcast wave bean shaping; Business beam shaping is formed at business time-slot, system forms multiple high-gain narrow beam according to the positional information of user, dynamically follow the tracks of multiple desired user, in the receiving mode, can be suppressed from the signal outside high-gain narrow beam, in the transmission mode, the signal power that desired user can be made to receive is maximum, and the interference simultaneously making the undesired user beyond narrow beam range of exposures be subject to is minimum.The application comparative maturity of current operation wave beam forming, as being widely used EBB (feature decomposition figuration) algorithm and GOB (fixed beam figuration) algorithm; Broadcast wave bean shaping is then the wave beam forming being carried out broadcast beam by the method for amendment broadcast beam weight.

For beam forming gain, the corresponding lobe width of large gain is narrow, the corresponding lobe width of little gain is wide, can find that gain has individual balance point: lobe width is narrow, for translational speed, very fast user cannot effectively follow the tracks of, lobe width is wide, can not effectively improve receiving terminal gain, effectively can not suppress the interference to other users.

There are the following problems for prior art: in TD-SCDMA system, smart antenna 8 antenna, when broadcast beam width is 65 °, broadcast wave bean shaping gain is 15dBi, business beam shaping gain is 22dBi, due to business beam shaping and broadcast wave bean shaping difference larger or inconsistent, have impact on covering power and the quality of TD-SCDMA network greatly; If adopt dual polarization high-gain aerial (65 °, 19dBi), although can promote broadcast beam covering power, business beam is not intelligent antenna figuration, and because TD-SCDMA is with frequently multiplexing, the interference in network increases to some extent.

Summary of the invention

The technical problem to be solved in the present invention is to provide a kind of signal receiving/transmission device and the method that adopt smart antenna, solve in prior art, business beam shaping and broadcast wave bean shaping difference larger or inconsistent, have impact on the covering power of TD-SCDMA network and the defect of quality greatly, realize the consistency between business beam shaping and broadcast wave bean shaping.

For solving the problems of the technologies described above, embodiments of the invention provide a kind of signal receiving/transmission device adopting smart antenna, comprise: aerial array, comprise N number of antenna element, each antenna element is connected with M weighter, client spatial correlation matrix unit, for determining the formed weighted network with M*N weighter; Weight vector solves unit, is connected with client spatial correlation matrix unit, for calculating weighted network weight matrix W based on described weighted network, for client k, calculates the weight vector W of client k according to described weighted network weight matrix W ^(k); Broadcast wave bean shaping switch unit, for adopting high-gain dual polarized antenna, arranges the weights of described high-gain dual polarized antenna; Business beam shaping switch unit, for by weight vector W ^(k)transposed matrix W ^{(k) T}with switching matrix D _nbe multiplied, obtain business beam weight vector D _n* W ^{(k) T}; Weighted network figuration unit, be connected with broadcast wave bean shaping switch unit, business beam shaping switch unit, for realizing broadcast wave bean shaping based on the weights of described high-gain dual polarized antenna in broadcast beam time slot, based on business beam weight vector D in business time-slot _n* W ^{(k) T}realize business beam shaping.

In described device, N is 8, comprises 6 unit smart antennas and 2 unit high-gain dual polarized antennas.

In described device, client spatial correlation matrix unit comprises matrix construction module; Matrix construction module, for according to following formula determination weighted network; Matrix X (t) is adopted to represent the signal of antenna array receiver, matrix W (t) is adopted to represent weighted network, matrix Y (t) is adopted to represent the signal that aerial array exports, relation Y (t)=W (t) X (t) is there is between the input and output of aerial array

$Y\left(t\right)={\left(\begin{array}{c}{y}_1\left(t\right)\\ y_2\left(t\right)\\ \·\\ \·\\ \·\\ y_M\left(t\right)\end{array}\right)}_{M\×1},W\left(t\right)={\left(\begin{array}{cccccc}{w}_1^{\left(1\right)}\left(t\right)& w_2^{\left(1\right)}\left(t\right)& \·& \·& \·& w_N^{\left(1\right)}\left(t\right)\\ w_1^{\left(2\right)}\left(t\right)& w_2^{\left(2\right)}\left(t\right)& \·& \·& \·& w_N^{\left(2\right)}\left(t\right)\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ w_1^{\left(M\right)}\left(t\right)& w_2^{\left(M\right)}\left(t\right)& \·& \·& \·& w_N^{\left(M\right)}\left(t\right)\end{array}\right)}_{M\×N},X\left(t\right)={\left(\begin{array}{c}{x}_1\left(t\right)\\ x_2{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ x_N\left(t\right)\end{array}\right)}_{N\×1}.$

In described device, client spatial correlation matrix unit is connected with channel estimating unit, and channel estimating unit is connected with M weighter of corresponding antenna element; Channel estimating unit, for setting up the relation between Received signal strength X (t) and the original transmission signal of each client, comprising: the original transmission signal of each client is s _m(t), m=1 ..., M, each original transmission signal s _mt radio channel response that () experiences is h ^{(m, n)}(t), m=1 ..., M, n=1 ..., N, for the n-th antenna element in described aerial array, the relation between Received signal strength X (t) and original transmission signal is the input signal x of antenna array receiver _n(t); N=1 ..., N is that the multipath signal superposition of multiple client is formed; Each original transmission signal has correlation at the channel response of different antennae unit,

$\left(\begin{array}{c}{h}^{(m,1)}\left(t\right)\\ h^{(m,2)}{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ h^{(m,N)}\left(t\right)\end{array}\right)=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}a\left({\mathrm{\θ}}_l^{\left(m\right)}\right)h_l^{\left(m\right)}=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\left(\begin{array}{c}{a}_1\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ a_2\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ \·\\ \·\\ \·\\ a_N\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\end{array}\right)h_l^{\left(m\right)},m=1,\·\·\·,M,$

Wherein, represent that the direction vector that described angle of arrival is corresponding, direction vector reflect the coefficient correlation caused because signal propagation distance is different between different antennae unit, represent the angle of arrival of the l article of multipath of client m, represent in employing single antenna reception situation, the radio channel response of the l article of multipath experience of client m.

In described device, weight vector solves unit and comprises: weight vector computing module, signal Y (t) for exporting according to aerial array equal or close to original transmission signal S (t) of client, should calculate the weighted network weight matrix W of weighted network W (t).

In described device, weight vector solves unit and comprises: eigenvector algorithm module, for obtaining signal space covariance matrix R _s; Obtain interference and spatial noise covariance matrix R _n;

Computing is performed to weighted network W (t) a weight vector W is found based on maximum power criterion ^(k), weight vector W ^(k)above-mentioned formula is made to reach maximum then weight vector W ^(k)signal space covariance matrix R _seigenvalue of maximum characteristic of correspondence vector; Wherein, (.) * represents the conjugation of complex vector, and (.) H represents the conjugate transpose of vector matrix.

Adopt a signal transmit-receive method for smart antenna, be applied to the device with aerial array, aerial array comprises N number of antenna element, and each antenna element is connected with M weighter, and method comprises: determine the formed weighted network with M*N weighter; Calculate weighted network weight matrix W based on described weighted network, calculate the weight vector W of client k according to described weighted network weight matrix W ^(k); For broadcast wave bean shaping, the weights of described high-gain dual polarized antenna are set; For business beam shaping, by weight vector W ^(k)transposed matrix W ^{(k) T}with switching matrix D _nbe multiplied, obtain business beam weight vector D _n* W ^{(k) T}; In broadcast beam time slot, realize broadcast wave bean shaping based on the weights of described high-gain dual polarized antenna, in business time-slot, realize business beam shaping based on described business beam weight vector.

In described method, N is 8, comprises 6 unit smart antennas, and high-gain dual polarized antenna described in Unit 2.

In described method, calculate weighted network weight matrix W based on described weighted network specifically to comprise: adopt matrix X (t) to represent the signal of antenna array receiver, matrix W (t) is adopted to represent weighted network, matrix Y (t) is adopted to represent the signal that aerial array exports, relation is there is: Y (t)=W (t) * X (t) between the input and output of aerial array

$Y\left(t\right)={\left(\begin{array}{c}{y}_1\left(t\right)\\ y_2\left(t\right)\\ \·\\ \·\\ \·\\ y_M\left(t\right)\end{array}\right)}_{M\×1},W\left(t\right)={\left(\begin{array}{cccccc}{w}_1^{\left(1\right)}\left(t\right)& w_2^{\left(1\right)}\left(t\right)& \·& \·& \·& w_N^{\left(1\right)}\left(t\right)\\ w_1^{\left(2\right)}\left(t\right)& w_2^{\left(2\right)}\left(t\right)& \·& \·& \·& w_N^{\left(2\right)}\left(t\right)\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ w_1^{\left(M\right)}\left(t\right)& w_2^{\left(M\right)}\left(t\right)& \·& \·& \·& w_N^{\left(M\right)}\left(t\right)\end{array}\right)}_{M\×N},X\left(t\right)={\left(\begin{array}{c}{x}_1\left(t\right)\\ x_2{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ x_N\left(t\right)\end{array}\right)}_{N\×1},$

The original transmission signal of each client is s _m(t), m=1 ..., M, each original transmission signal s _mt radio channel response that () experiences is h ^{(m, n)}(t), m=1 ..., M, n=1 ..., N, for the n-th antenna element in described aerial array, the relation between Received signal strength X (t) and original transmission signal is the input signal x of antenna array receiver _n(t), n=1 ..., N is that the multipath signal superposition of multiple client is formed; Each original transmission signal has correlation at the channel response of different antennae unit,

$\left(\begin{array}{c}{h}^{(m,1)}\left(t\right)\\ h^{(m,2)}{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ h^{(m,N)}\left(t\right)\end{array}\right)=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}a\left({\mathrm{\θ}}_l^{\left(m\right)}\right)h_l^{\left(m\right)}=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\left(\begin{array}{c}{a}_1\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ a_2\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ \·\\ \·\\ \·\\ a_N\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\end{array}\right)h_l^{\left(m\right)},m=1,\·\·\·,M,$

Wherein, represent that the direction vector that described angle of arrival is corresponding, direction vector reflect the coefficient correlation caused because signal propagation distance is different between different antennae unit, represent the angle of arrival of the l article of multipath of client m, represent in employing single antenna reception situation, the radio channel response of the l article of multipath experience of client m; Equal or close to original transmission signal S (t) of client, the weighted network weight matrix W of weighted network W (t) should be calculated according to signal Y (t) that aerial array exports.

In described method, calculate the weight vector W of client k according to described weighted network weight matrix W ^(k)specifically comprise: obtain signal space covariance matrix R _s; Obtain interference and spatial noise covariance matrix R _n; Computing is performed to weighted network W (t) a weight vector W is found based on maximum power criterion ^(k), weight vector W ^(k)above-mentioned formula is made to reach maximum then weight vector W ^(k)signal space covariance matrix R _seigenvalue of maximum characteristic of correspondence vector; Wherein, (.) * represents the conjugation of complex vector, and (.) H represents the conjugate transpose of vector matrix.

The beneficial effect of technique scheme of the present invention is as follows: adopt dual polarization high-gain aerial (65 ° at time slot broadcast beam, 19dBi), 6 unit intelligent antenna figuration 21dBi are adopted at business time-slot business beam, thus to reach broadcast beam gain be 19dBi, business beam shaping is the effect of 21dBi, improves the covering power of TD network and the quality of network.

Accompanying drawing explanation

Fig. 1 represents the weighted network schematic diagram of smart antenna;

Fig. 2 represents a kind of structural representation adopting the signal receiving/transmission device of smart antenna;

Fig. 3 represents time slot and business time-slot relation schematic diagram;

Fig. 4 represents the antenna array structure schematic diagram of 8 antenna elements;

Fig. 5 represents a kind of method flow schematic diagram adopting the signal receiving/transmission device of smart antenna.

Embodiment

For making the technical problem to be solved in the present invention, technical scheme and advantage clearly, be described in detail below in conjunction with the accompanying drawings and the specific embodiments.

Smart antenna is a kind of array antenna be made up of multiple antenna element, the antenna pattern of array is changed by the weighted amplitude and phase place regulating each antenna element signal, thus suppress interference, improve signal interference ratio, in a broad sense, intelligent antenna technology is the technology of mating for the optimal spatial of antenna and communication environments and user and base station.

As shown in Figure 1, weighted network is made up of N number of antenna element, and each antenna element has M to overlap weighter (a corresponding M user), and can form the wave beam of M different directions, number of users M can be greater than antenna element number N.In receiving course, connect a weighter after each antenna, be namely multiplied by a coefficient, coefficient is normally plural, the not only amplitude of accommodation but also control phase; Or connect a time delay tap weighted network (identical with time domain FIR equalizer in structure), usually, these weight coefficients can appropriately change, self-adaptative adjustment, finally merges with adder, has carried out the Combined Treatment of airspace filter or spatial domain and time domain.

In emission process, before weighter or weighted network are placed in antenna, adder is not had to merge.

Due to the descending bottleneck of TD-SCDMA link budget mainly broadcast beam Primary Common Control Physical Channel (PCCPCH), up bottleneck is ascending pilot frequency physical channel (UPPCH) mainly, in the embodiment of the present invention, based on the notable difference of intelligent antenna business beam figuration gain and broadcast wave bean shaping gain, realize the consistency of business beam shaping and broadcast wave bean shaping.

N number of antenna element,

Each antenna element is connected with M weighter, and M*N weighter forms weighted network;

The signal of antenna array receiver adopts matrix X (t) to represent, weighted network adopts matrix W (t) to represent, aerial array exports and represents to there is relation between the input and output of smart antenna with matrix Y (t):

Y (t)=W (t) X (t) formula 1

$Y\left(t\right)={\left(\begin{array}{c}{y}_1\left(t\right)\\ y_2\left(t\right)\\ \·\\ \·\\ \·\\ y_M\left(t\right)\end{array}\right)}_{M\×1},W\left(t\right)={\left(\begin{array}{cccccc}{w}_1^{\left(1\right)}\left(t\right)& w_2^{\left(1\right)}\left(t\right)& \·& \·& \·& w_N^{\left(1\right)}\left(t\right)\\ w_1^{\left(2\right)}\left(t\right)& w_2^{\left(2\right)}\left(t\right)& \·& \·& \·& w_N^{\left(2\right)}\left(t\right)\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ w_1^{\left(M\right)}\left(t\right)& w_2^{\left(M\right)}\left(t\right)& \·& \·& \·& w_N^{\left(M\right)}\left(t\right)\end{array}\right)}_{M\×N},X\left(t\right)={\left(\begin{array}{c}{x}_1\left(t\right)\\ x_2{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ x_N\left(t\right)\end{array}\right)}_{N\×1}$ Formula 2

To each coefficient in weighted network adjust, make each output function y _m(t), m=1 ..., M exports according to desired target;

In mobile communication system, the input signal (x of antenna array receiver _n(t); N=1 ..., N) and the superposition of multipath signal of normally multiple user.The original transmission signal of user is s _m(t); M=1 ..., M, the radio channel response of each user's experience is h ^{(m, n)}(t), m=1 ..., M, n=1 ..., N, so, the relation between the input signal of aerial array and the original transmission signal of each user can be expressed as

$x_n\left(t\right)=\underset{m=1}{\overset{M}{\mathrm{\Σ}}}(s_m\left(t\right)\⊗h^{(m,n)}\left(t\right)),n=1,\·\·\·,N$ Formula 3

For smart antenna, because the distance between antenna element is very near, is about 0.5 times of carrier wavelength, makes every user channel response on different antennas have correlation, namely

$\left(\begin{array}{c}{h}^{(m,1)}\left(t\right)\\ h^{(m,2)}{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ h^{(m,N)}\left(t\right)\end{array}\right)=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}a\left({\mathrm{\θ}}_l^{\left(m\right)}\right)h_l^{\left(m\right)}=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\left(\begin{array}{c}{a}_1\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ a_2\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ \·\\ \·\\ \·\\ a_N\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\end{array}\right)h_l^{\left(m\right)},m=1,\·\·\·,M$ Formula 4

Wherein, represent the angle of arrival of the l article of multipath of m user, represent the direction vector that described angle of arrival is corresponding, it reflects the coefficient correlation caused because signal propagation distance is different between different antennae unit, represent in employing single antenna reception situation, the radio channel response of the l article of multipath experience of m user.

Intelligent antenna technology is by adjusting each above-mentioned weights, realize space filtering to each user, thus be separated each user and recover the transmission signal of each user, namely, output function is equaled or as far as possible close to the original transmission signal of user, is expressed as with mathematical formulae

Y _m(t)=s _m(t), m=1 ..., M formula 5

According to outputing signal the different-effect reached after weighed value adjusting, the application of intelligent antenna technology is roughly divided into following two classes: one is that maximum power ratio merges; Two is wave beam formings.Maximum power ratio merges the space diversity effect mainly playing signal, is more suitable for the situation that signal interference ratio is higher.Wave beam forming then mainly plays track user, suppresses the effect of interference, and the angle of arrival being more suitable for signal interference ratio the unknown and each user can distinct situation.

The forming algorithm of smart antenna mainly comprises:

GOB (Grid Of Beam) algorithm, also known as beam scanning method, is the algorithm based on parameter model (utilizing the spatial domain parameter of channel), makes base station realize descending directional transmissions.The basic ideas of GOB algorithm:

Whole space is divided into L region, and an initial angle is set for each region.With the direction vector of the initial angle of regional for weight coefficient, calculate received signal power, then find the region that maximum power is corresponding, then the initial angle in this region is used as the angle of arrival of estimation.Utilize the feature of up-downgoing channel symmetry, determine figuration angle.

EBB (Eigenvalue Based Beamforming) algorithm, also known as characteristic vector method: the signal to noise ratio received with desired user maximizes as criterion, obtain best weight of downgoing emission, this weight of downgoing emission is the eigenvalue of maximum characteristic of correspondence vector of signal covariance matrix.Weight vector is obtained by decomposition spatial correlation matrix being carried out to characteristic value.Implementation method finds the weight vector W of a kth user ^(k), make W _oPTmaximum.

$W_{\mathrm{opt}}=\underset{W}{\max }\left(\frac{W^H{R}_{s}W}{W^H{R}_{n}W}\right)$ Formula 6

Wherein, (.) * represents the conjugation of complex vector, and (.) H represents the conjugate transpose of vector matrix, and the target based on maximum power criterion is that searching weight vectors makes formula 2 reach maximum:

W _oPTimplication be goal seeking weight vectors W based on maximum power criterion ^(k)make formula 6) reach maximum.R _srepresent signal space covariance matrix, R _nrepresent interference and spatial noise covariance matrix, known by the relevant knowledge of matrix, make the W that formula 6 is maximum ^(k)solution be unique, namely optimum weight vector is signal space covariance matrix R _seigenvalue of maximum characteristic of correspondence vector.

For solving business beam shaping (business time-slot) and broadcast wave bean shaping (time slot) conforming problem, based on the notable difference of intelligent antenna business beam gain and broadcast beam gain, in broadcast wave bean shaping process, adopt dual polarization high-gain aerial, in business beam shaping process, adopt 6 unit intelligent antenna figuration (business time-slot) 21dBi.

The embodiment of the present invention provides a kind of signal receiving/transmission device adopting smart antenna, as shown in Figure 2, comprising:

Aerial array, comprises N number of antenna element, and each antenna element is connected with M weighter,

Client spatial correlation matrix unit, for determining the formed weighted network with M*N weighter;

Weight vector solves unit, is connected with client spatial correlation matrix unit, for calculating weighted network weight matrix W based on described weighted network, for client k, calculates the weight vector W of client k according to described weighted network weight matrix W ^(k);

Broadcast wave bean shaping switch unit, for adopting high-gain dual polarized antenna, arranges the weights of described high-gain dual polarized antenna;

Business beam shaping switch unit, for by weight vector W ^(k)transposed matrix W ^{(k) T}with switching matrix D _nbe multiplied, obtain business beam weight vector D _n* W ^{(k) T};

Weighted network figuration unit, be connected with broadcast wave bean shaping switch unit, business beam shaping switch unit, for realizing broadcast wave bean shaping based on the weights of described high-gain dual polarized antenna in broadcast beam time slot, based on described business beam weight vector D in business time-slot _n* W ^{(k) T}realize business beam shaping.

The technology that Application Example technical scheme provides, as shown in Figure 3, dual polarization high-gain aerial (65 ° is adopted at time slot broadcast beam, 19dBi), 6 unit intelligent antenna figuration 21dBi are adopted at business time-slot business beam, thus to reach broadcast beam gain be 19dBi, business beam shaping is the effect of 21dBi, improves the covering power of TD network and the quality of network.

In a preferred embodiment, as shown in Figure 4, N is 8, comprises 6 unit smart antennas, and 2 unit high-gain dual polarized antennas.

Determine that the formed weighted network with M*N weighter refers to, specifically determine the parts that weighted network should comprise, in the embodiment of the present invention, weighted network comprises M*N weighter.

In a preferred embodiment, client spatial correlation matrix unit comprises matrix construction module;

Matrix construction module, for

Matrix X (t) is adopted to represent the signal of antenna array receiver,

Matrix W (t) is adopted to represent weighted network,

Matrix Y (t) is adopted to represent the signal that aerial array exports,

Relation is there is: Y (t)=W (t) X (t) formula 1 between the input and output of aerial array

$Y\left(t\right)={\left(\begin{array}{c}{y}_1\left(t\right)\\ y_2\left(t\right)\\ \·\\ \·\\ \·\\ y_M\left(t\right)\end{array}\right)}_{M\×1},W\left(t\right)={\left(\begin{array}{cccccc}{w}_1^{\left(1\right)}\left(t\right)& w_2^{\left(1\right)}\left(t\right)& \·& \·& \·& w_N^{\left(1\right)}\left(t\right)\\ w_1^{\left(2\right)}\left(t\right)& w_2^{\left(2\right)}\left(t\right)& \·& \·& \·& w_N^{\left(2\right)}\left(t\right)\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ w_1^{\left(M\right)}\left(t\right)& w_2^{\left(M\right)}\left(t\right)& \·& \·& \·& w_N^{\left(M\right)}\left(t\right)\end{array}\right)}_{M\×N},X\left(t\right)={\left(\begin{array}{c}{x}_1\left(t\right)\\ x_2{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ x_N\left(t\right)\end{array}\right)}_{N\×1}$ Formula 2.

To each coefficient in weighted network adjustment, makes each output function (y _m(t); M=1 ..., M) export according to desired target; In mobile communication system, the input signal (x of antenna array receiver _n(t); N=1 ..., N) and the superposition of multipath signal of normally multiple user.

In a preferred embodiment, client spatial correlation matrix unit is connected with channel estimating unit, and channel estimating unit is connected with M weighter of corresponding antenna element;

Channel estimating unit, for setting up the relation between Received signal strength X (t) and the original transmission signal of each client, comprising:

The original transmission signal of each client is s _m(t), m=1 ..., M,

Each original transmission signal s _mt radio channel response that () experiences is h ^{(m, n)}(t), m=1 ..., M, n=1 ..., N,

For the n-th antenna element in described aerial array, the relation between Received signal strength X (t) and original transmission signal is: $x_n\left(t\right)=\underset{m=1}{\overset{M}{\mathrm{\Σ}}}(s_m\left(t\right)\⊗h^{(m,n)}\left(t\right)),n=1,\·\·\·,N$ Formula 3

The input signal x of antenna array receiver _n(t); N=1 ..., N is that the multipath signal superposition of multiple client is formed;

Each original transmission signal has correlation at the channel response of different antennae unit,

$\left(\begin{array}{c}{h}^{(m,1)}\left(t\right)\\ h^{(m,2)}{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ h^{(m,N)}\left(t\right)\end{array}\right)=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}a\left({\mathrm{\θ}}_l^{\left(m\right)}\right)h_l^{\left(m\right)}=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\left(\begin{array}{c}{a}_1\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ a_2\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ \·\\ \·\\ \·\\ a_N\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\end{array}\right)h_l^{\left(m\right)},m=1,\·\·\·,M$ Formula 4

Wherein, represent that the direction vector that described angle of arrival is corresponding, direction vector reflect the coefficient correlation caused because signal propagation distance is different between different antennae unit, represent the angle of arrival of the l article of multipath of client m, represent in employing single antenna reception situation, the radio channel response of the l article of multipath experience of client m.

In a preferred embodiment, weight vector solves unit and comprises:

Weight vector computing module, equal or close to original transmission signal S (t) of client, should calculate the weighted network weight matrix W of weighted network W (t) for signal Y (t) exported according to aerial array.

Intelligent antenna technology is by adjusting each above-mentioned weights, realize space filtering to each user, thus be separated each user and recover the transmission signal of each user, namely, output function is equaled or tries one's best close to the original transmission signal of user, mathematical formulae is y _m(t)=s _m(t), m=1 ..., M formula 5

In a preferred embodiment, weight vector solves unit and comprises:

Eigenvector algorithm module, for obtaining signal space covariance matrix R _s;

Obtain interference and spatial noise covariance matrix R _n;

Computing is performed to weighted network W (t)

A weight vector W is found based on maximum power criterion ^(k), weight vector W ^(k)above-mentioned formula is made to reach maximum $W_{\mathrm{opt}}=\underset{W}{\max }\left(\frac{W^H{R}_{s}W}{W^H{R}_{n}W}\right)$ Formula 6

Then weight vector W ^(k)signal space covariance matrix R _seigenvalue of maximum characteristic of correspondence vector; Wherein, (.) * represents the conjugation of complex vector, and (.) H represents the conjugate transpose of vector matrix.

According to outputing signal the different-effect reached after weighed value adjusting, the application of intelligent antenna technology is roughly divided into following two classes: one is that maximum power ratio merges; Two is wave beam formings.Maximum power ratio merges the space diversity effect mainly playing signal, is more suitable for the situation that signal interference ratio is higher.Wave beam forming then mainly plays track user, suppresses the effect of interference, and the angle of arrival being more suitable for signal interference ratio the unknown and each user can distinct situation.

In an application scenarios, TD composite intelligent antenna as shown in Figure 4, comprising: dual polarization 6 unit smart antenna and 2 unit high-gain aerials.

TD combined intelligent antenna is made up of dual polarization 6 unit smart antenna and 2 unit high-gain dual polarized antennas.Dual-polarization intelligent antenna port one, 2; 3,4; 5,6; For original 6 port smart antennas, port 7,8 is high-gain smart antenna.

Broadcast wave bean shaping (time slot) switches with high-gain dual polarized antenna (65 °, 19dBi) weights Wk is arranged: broadcast wave bean shaping is switching high-gain dual polarized antenna (65 °, 19dBi) in broadcast beam time slot.Switching high-gain dual polarized antenna weights Wk is set, broadcast wave bean shaping (time slot) is switched on high-gain dual polarized antenna (65 °, 19dBi).

Be increased to 19dBi in order to ensure broadcast beam gain from 15dBi, add port 7,8 for high-gain dual polarized antenna.And arrange at dual-polarization intelligent antenna broadcast beam wave beam weight and innovate, the directional diagram of broadcast beam is made to switch to dual polarization high-gain aerial 19dBi, in order to make broadcast beam use dual polarization high-gain aerial, the weights Wk of broadcast beam is arranged: port one, 2; 3,4; 5,6 amplitude and phase place be set to 0, port 7,8 amplitude is set to 1, and phase place is set to 0.

Business beam shaping (business time-slot) is switching dual polarization 6 unit intelligent antenna algorithm in business beam time slot:

By EBB (Eigenvalue Based Beamforming) algorithm-characteristic vector method: obtain weight vector by decomposition spatial correlation matrix being carried out to characteristic value.Implementation method finds the weight vector W of a kth user ^{(k) T}, the weight vector W of the kth user tried to achieve ^(k),

Obtain maximum characteristic vector W ^{(k) T}, be multiplied by switching matrix $D_n=\left[\begin{array}{cccccccc}1& 0& 0& 0& 0& 0& 0& 0\\ 0& 1& 0& 0& 0& 0& 0& 0\\ 0& 0& 1& 0& 0& 0& 0& 0\\ 0& 0& 0& 1& 0& 0& 0& 0\\ 0& 0& 0& 0& 1& 0& 0& 0\\ 0& 0& 0& 0& 0& 1& 0& 0\\ 0& 0& 0& 0& 0& 0& 0& 0\\ 0& 0& 0& 0& 0& 0& 0& 0\end{array}\right]$

N=8, be namely 8 ports, (.) T represents the transposition of vector (matrix).

Selection matrix D is switched by taking advantage of _nobtain business beam weight vector D _n* W ^{(k) T}formula 7

Make business time-slot be operated on dual polarization 6 unit smart antenna, k is the weights of a kth customer service wave beam forming.

It is 19dBi that above-mentioned technology can realize TD system broadcasts wave beam forming (time slot) gain, business beam shaping (business time-slot) about 21dBi, so, promotes network broadcast channel covering power 4dB.

The technology provided may be used in TD-LTE system equally.TD-LTE system and TD-SCDMA system are all time-division system and the frame structure of network is closely similar, and TD-SCDMA covers not enough problem, and TD-LTE exists equally, therefore may be used for equally in TD-LTE system.

The embodiment of the present invention provides a kind of signal transmit-receive method adopting smart antenna, is applied to the device with aerial array, and aerial array comprises N number of antenna element, and each antenna element is connected with M weighter, and as shown in Figure 5, method comprises:

Step 501, determines the formed weighted network with M*N weighter;

Step 502, calculates weighted network weight matrix W based on described weighted network, calculates the weight vector W of client k according to described weighted network weight matrix W ^(k);

Step 503, for broadcast wave bean shaping, arranges the weights of described high-gain dual polarized antenna; For business beam shaping, by weight vector W ^(k)transposed matrix W ^{(k) T}with switching matrix D _nbe multiplied, obtain business beam weight vector D _n* W ^{(k) T};

Step 504, realizes broadcast wave bean shaping based on the weights of described high-gain dual polarized antenna in broadcast beam time slot, in business time-slot, realize business beam shaping based on described business beam weight vector.

In a preferred embodiment, N is 8, comprises 6 unit smart antennas, and high-gain dual polarized antenna described in Unit 2.

In a preferred embodiment, calculate weighted network weight matrix W based on described weighted network and specifically comprise: adopt matrix X (t) to represent the signal of antenna array receiver,

Matrix W (t) is adopted to represent weighted network,

Matrix Y (t) is adopted to represent the signal that aerial array exports,

Relation Y (t)=W (t) X (t) formula 1 is there is between the input and output of aerial array

$Y\left(t\right)={\left(\begin{array}{c}{y}_1\left(t\right)\\ y_2\left(t\right)\\ \·\\ \·\\ \·\\ y_M\left(t\right)\end{array}\right)}_{M\×1},W\left(t\right)={\left(\begin{array}{cccccc}{w}_1^{\left(1\right)}\left(t\right)& w_2^{\left(1\right)}\left(t\right)& \·& \·& \·& w_N^{\left(1\right)}\left(t\right)\\ w_1^{\left(2\right)}\left(t\right)& w_2^{\left(2\right)}\left(t\right)& \·& \·& \·& w_N^{\left(2\right)}\left(t\right)\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ w_1^{\left(M\right)}\left(t\right)& w_2^{\left(M\right)}\left(t\right)& \·& \·& \·& w_N^{\left(M\right)}\left(t\right)\end{array}\right)}_{M\×N},X\left(t\right)={\left(\begin{array}{c}{x}_1\left(t\right)\\ x_2{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ x_N\left(t\right)\end{array}\right)}_{N\×1}$ Formula 2

The original transmission signal of each client is s _m(t), m=1 ..., M,

Each original transmission signal s _mt radio channel response that () experiences is h ^{(m, n)}(t), m=1 ..., M, n=1 ..., N,

For the n-th antenna element in described aerial array, the relation between Received signal strength X (t) and original transmission signal is $x_n\left(t\right)=\underset{m=1}{\overset{M}{\mathrm{\Σ}}}(s_m\left(t\right)\⊗h^{(m,n)}\left(t\right)),n=1,\·\·\·,N$ Formula 3

The input signal x of antenna array receiver _n(t); N=1 ..., N is that the multipath signal superposition of multiple client is formed;

Each original transmission signal has correlation at the channel response of different antennae unit,

$\left(\begin{array}{c}{h}^{(m,1)}\left(t\right)\\ h^{(m,2)}{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ h^{(m,N)}\left(t\right)\end{array}\right)=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}a\left({\mathrm{\θ}}_l^{\left(m\right)}\right)h_l^{\left(m\right)}=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\left(\begin{array}{c}{a}_1\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ a_2\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ \·\\ \·\\ \·\\ a_N\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\end{array}\right)h_l^{\left(m\right)},m=1,\·\·\·,M$ Formula 4

Wherein, represent that the direction vector that described angle of arrival is corresponding, direction vector reflect the coefficient correlation caused because signal propagation distance is different between different antennae unit, represent the angle of arrival of the l article of multipath of client m, represent in employing single antenna reception situation, the radio channel response of the l article of multipath experience of client m;

Equal or close to original transmission signal S (t) of client, the weighted network weight matrix W of weighted network W (t) should be calculated according to signal Y (t) that aerial array exports.

In a preferred embodiment, the weight vector W of client k is calculated according to described weighted network weight matrix W ^(k)specifically comprise:

Obtain signal space covariance matrix R _s;

Obtain interference and spatial noise covariance matrix R _n;

Computing is performed to weighted network W (t)

A weight vector W is found based on maximum power criterion ^{(k) T}, weight vector W ^{(k) T}above-mentioned formula is made to reach maximum $W_{\mathrm{opt}}=\underset{W}{\max }\left(\frac{W^H{R}_{s}W}{W^H{R}_{n}W}\right)$ Formula 6

Then weight vector W ^(k)signal space covariance matrix R _seigenvalue of maximum characteristic of correspondence vector; Wherein, (.) * represents the conjugation of complex vector, and (.) H represents the conjugate transpose of vector matrix.

Advantage after employing this programme is: broadcast wave bean shaping is in broadcast beam time slot, be switched to high-gain dual polarized antenna (65 °, 19dBi) carry out broadcast beam, business beam shaping is in business beam time slot, be switched to dual polarization 6 unit smart antenna, that this compensate for general unit 8 and 6 unit broadcast beam of smart antenna and business beam gain is inconsistent-and broadcast wave bean shaping gain is 15dBi, the shortcoming of business beam shaping 21dBi.By COST231 propagation model computation-intensive city, under link budget promotes 4dB situation, base station coverage distance rises to 0.36KM from 0.27KM, under identical covering index, for 200 square kilometres of areas, base station number drops to 594 from 1056, decreases nearly 1 times.

The above is the preferred embodiment of the present invention; it should be pointed out that for those skilled in the art, under the prerequisite not departing from principle of the present invention; can also make some improvements and modifications, these improvements and modifications also should be considered as protection scope of the present invention.

Claims (10)

1. adopt a signal receiving/transmission device for smart antenna, it is characterized in that, comprising:

Aerial array, comprises N number of antenna element, and each antenna element is connected with M weighter,

Client spatial correlation matrix unit, for determining the formed weighted network with M*N weighter;

Weight vector solves unit, is connected with client spatial correlation matrix unit, for calculating weighted network weight matrix W based on described weighted network, for client k, calculates the weight vector W of client k according to described weighted network weight matrix W ^(k);

Broadcast wave bean shaping switch unit, for adopting high-gain dual polarized antenna, arranges the weights of described high-gain dual polarized antenna;

Business beam shaping switch unit, for by weight vector W ^(k)transposed matrix W ^{(k) T}with switching matrix D _nbe multiplied, obtain business beam weight vector D _n* W ^{(k) T};

Weighted network figuration unit, be connected with broadcast wave bean shaping switch unit, business beam shaping switch unit, for realizing broadcast wave bean shaping based on the weights of described high-gain dual polarized antenna in broadcast beam time slot, based on described business beam weight vector D in business time-slot _n* W ^{(k) T}realize business beam shaping.

2. device according to claim 1, is characterized in that,

N is 8, comprises 6 unit smart antennas and 2 unit high-gain dual polarized antennas.

3. device according to claim 1, is characterized in that, client spatial correlation matrix unit comprises matrix construction module;

Matrix construction module, for according to following formula determination weighted network;

Matrix X (t) is adopted to represent the signal of antenna array receiver,

Matrix W (t) is adopted to represent weighted network,

Matrix Y (t) is adopted to represent the signal that aerial array exports,

Relation Y (t)=W (t) X (t) is there is between the input and output of aerial array

$Y\left(t\right)={\left(\begin{array}{c}{y}_1\left(t\right)\\ y_2\left(t\right)\\ \·\\ \·\\ \·\\ y_M\left(t\right)\end{array}\right)}_{M\×1},W\left(t\right)={\left(\begin{array}{cccccc}{w}_1^{\left(1\right)}\left(t\right)& w_2^{\left(1\right)}\left(t\right)& \·& \·& \·& w_N^{\left(1\right)}\left(t\right)\\ w_1^{\left(2\right)}\left(t\right)& w_2^{\left(2\right)}\left(t\right)& \·& \·& \·& w_N^{\left(2\right)}\left(t\right)\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ w_1^{\left(M\right)}\left(t\right)& w_2^{\left(M\right)}\left(t\right)& \·& \·& \·& w_N^{\left(M\right)}\left(t\right)\end{array}\right)}_{M\×N},X\left(t\right)={\left(\begin{array}{c}{x}_1\left(t\right)\\ x_2{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ x_N\left(t\right)\end{array}\right)}_{N\×1}.$

4. device according to claim 3, is characterized in that, client spatial correlation matrix unit is connected with channel estimating unit, and channel estimating unit is connected with M weighter of corresponding antenna element;

Channel estimating unit, for setting up the relation between Received signal strength X (t) and the original transmission signal of each client, comprising:

The original transmission signal of each client is s _m(t), m=1 ..., M,

Each original transmission signal s _mt radio channel response that () experiences is h ^{(m, n)}(t), m=1 ..., M, n=1 ..., N,

For the n-th antenna element in described aerial array, the relation between Received signal strength X (t) and original transmission signal is $x_n\left(t\right)=\underset{m=1}{\overset{M}{\mathrm{\Σ}}}(s_m\left(t\right)\⊗h^{(m,n)}\left(t\right)),n=1,\·\·\·,N,$

The input signal x of antenna array receiver _n(t); N=1 ..., N is that the multipath signal superposition of multiple client is formed;

Each original transmission signal has correlation at the channel response of different antennae unit,

$\left(\begin{array}{c}{h}^{(m,1)}\left(t\right)\\ h^{(m,2)}{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ h^{(m,N)}\left(t\right)\end{array}\right)=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}a\left({\mathrm{\θ}}_l^{\left(m\right)}\right)h_l^{\left(m\right)}=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\left(\begin{array}{c}{a}_1\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ a_2\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ \·\\ \·\\ \·\\ a_N\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\end{array}\right)h_l^{\left(m\right)},m=1,\·\·\·,M,$

Wherein, represent that the direction vector that described angle of arrival is corresponding, direction vector reflect the coefficient correlation caused because signal propagation distance is different between different antennae unit, represent the angle of arrival of the l article of multipath of client m, represent in employing single antenna reception situation, the radio channel response of the l article of multipath experience of client m.

5. device according to claim 4, is characterized in that, weight vector solves unit and comprises:

Weight vector computing module, equal or close to original transmission signal S (t) of client, should calculate the weighted network weight matrix W of weighted network W (t) for signal Y (t) exported according to aerial array.

6. device according to claim 5, is characterized in that, weight vector solves unit and comprises:

Eigenvector algorithm module, for obtaining signal space covariance matrix R _s;

Obtain interference and spatial noise covariance matrix R _n;

Computing is performed to weighted network W (t)

A weight vector W is found based on maximum power criterion ^(k), weight vector W ^(k)above-mentioned formula is made to reach maximum $W_{\mathrm{opt}}=\underset{W}{\max }\left(\frac{W^H{R}_{s}W}{W^H{R}_{n}W}\right),$

Then weight vector W ^(k)signal space covariance matrix R _seigenvalue of maximum characteristic of correspondence vector; Wherein, (.) * represents the conjugation of complex vector, and (.) H represents the conjugate transpose of vector matrix.

7. adopt a signal transmit-receive method for smart antenna, it is characterized in that, be applied to the device with aerial array, aerial array comprises N number of antenna element, and each antenna element is connected with M weighter, and method comprises:

Determine the formed weighted network with M*N weighter;

Calculate weighted network weight matrix W based on described weighted network, calculate the weight vector W of client k according to described weighted network weight matrix W ^(k);

For broadcast wave bean shaping, the weights of described high-gain dual polarized antenna are set; For business beam shaping, by weight vector W ^(k)transposed matrix W ^{(k) T}with switching matrix D _nbe multiplied, obtain business beam weight vector D _n* W ^{(k) T};

In broadcast beam time slot, realize broadcast wave bean shaping based on the weights of described high-gain dual polarized antenna, in business time-slot, realize business beam shaping based on described business beam weight vector.

8. method according to claim 7, is characterized in that,

N is 8, comprises 6 unit smart antennas, and high-gain dual polarized antenna described in Unit 2.

9. method according to claim 7, is characterized in that, calculates weighted network weight matrix W specifically comprise based on described weighted network:

Matrix X (t) is adopted to represent the signal of antenna array receiver,

Matrix W (t) is adopted to represent weighted network,

Matrix Y (t) is adopted to represent the signal that aerial array exports,

Relation is there is: Y (t)=W (t) * X (t) between the input and output of aerial array,

$Y\left(t\right)={\left(\begin{array}{c}{y}_1\left(t\right)\\ y_2\left(t\right)\\ \·\\ \·\\ \·\\ y_M\left(t\right)\end{array}\right)}_{M\×1},W\left(t\right)={\left(\begin{array}{cccccc}{w}_1^{\left(1\right)}\left(t\right)& w_2^{\left(1\right)}\left(t\right)& \·& \·& \·& w_N^{\left(1\right)}\left(t\right)\\ w_1^{\left(2\right)}\left(t\right)& w_2^{\left(2\right)}\left(t\right)& \·& \·& \·& w_N^{\left(2\right)}\left(t\right)\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ \·& \·& & \·& & \·\\ w_1^{\left(M\right)}\left(t\right)& w_2^{\left(M\right)}\left(t\right)& \·& \·& \·& w_N^{\left(M\right)}\left(t\right)\end{array}\right)}_{M\×N},X\left(t\right)={\left(\begin{array}{c}{x}_1\left(t\right)\\ x_2{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ x_N\left(t\right)\end{array}\right)}_{N\×1},$

The original transmission signal of each client is s _m(t), m=1 ..., M,

Each original transmission signal s _mt radio channel response that () experiences is h ^{(m, n)}(t), m=1 ... M, n=1 ..., N,

For the n-th antenna element in described aerial array, the relation between Received signal strength X (t) and original transmission signal is $x_n\left(t\right)=\underset{m=1}{\overset{M}{\mathrm{\Σ}}}(s_m\left(t\right)\⊗h^{(m,n)}\left(t\right)),n=1,\·\·\·,N,$

The input signal x of antenna array receiver _n(t), n=1 ..., N is that the multipath signal superposition of multiple client is formed;

Each original transmission signal has correlation at the channel response of different antennae unit,

$\left(\begin{array}{c}{h}^{(m,1)}\left(t\right)\\ h^{(m,2)}{\left(t\right)}_{}\\ \·\\ \·\\ \·\\ h^{(m,N)}\left(t\right)\end{array}\right)=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}a\left({\mathrm{\θ}}_l^{\left(m\right)}\right)h_l^{\left(m\right)}=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\left(\begin{array}{c}{a}_1\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ a_2\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\\ \·\\ \·\\ \·\\ a_N\left({\mathrm{\θ}}_l^{\left(m\right)}\right)\end{array}\right)h_l^{\left(m\right)},m=1,\·\·\·,M,$

Wherein, represent that the direction vector that described angle of arrival is corresponding, direction vector reflect the coefficient correlation caused because signal propagation distance is different between different antennae unit, represent the angle of arrival of the l article of multipath of client m, represent in employing single antenna reception situation, the radio channel response of the l article of multipath experience of client m;

Equal or close to original transmission signal S (t) of client, the weighted network weight matrix W of weighted network W (t) should be calculated according to signal Y (t) that aerial array exports.

10. method according to claim 7, is characterized in that, calculates the weight vector W of client k according to described weighted network weight matrix W ^(k)specifically comprise:

Obtain signal space covariance matrix R _s;

Obtain interference and spatial noise covariance matrix R _n;

Computing is performed to weighted network W (t)

A weight vector W is found based on maximum power criterion ^(k), weight vector W ^(k)above-mentioned formula is made to reach maximum $W_{\mathrm{opt}}=\underset{W}{\max }\left(\frac{W^H{R}_{s}W}{W^H{R}_{n}W}\right),$

Then weight vector W ^(k)signal space covariance matrix R _seigenvalue of maximum characteristic of correspondence vector;

Wherein, (.) * represents the conjugation of complex vector, and (.) H represents the conjugate transpose of vector matrix.