CN104618292A - MIMO-OFDM (Multiple Input Multiple Output-Orthogonal Frequency Division Multiplexing) system based detection method and device - Google Patents
MIMO-OFDM (Multiple Input Multiple Output-Orthogonal Frequency Division Multiplexing) system based detection method and device Download PDFInfo
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Abstract
The invention discloses an MIMO-OFDM (Multiple Input Multiple Output-Orthogonal Frequency Division Multiplexing) system based detection method and device so as to enable different detection modes to be flexibly utilized according to different modulation modes through a system. The MIMO-OFDM system based detection method comprises performing detection on high-order modulation signals received by a first detection method and performing detection on low-order modulation signal received by a second detection method, wherein the first detection algorithm is suitable for a parallel programmable structure and the defects of the first detection algorithm in the low-order modulation signal detection are overcome by the second detection algorithm. According to the MIMO-OFDM system based detection method and device, rates required by different conditions can be supported by the different modulation modes, the different detection methods are adopted according to the different modulation modes, and accordingly the performance of the system can be improved on the premise of simple implementation.
Description
Technical field
The present invention relates to wireless communication field, more specifically, relate to signal detecting method and the device of the system of a kind of multiple-input and multiple-output (Multiple Input Multiple Output, MIMO) technology and OFDM (Orthogonal Frequency Division Multiplexing) combine with technique.
Background technology
Future mobile communication system requires to hold user as much as possible in certain frequency band, and the transmission rate of data will reach 10 ~ 100Mbits/s.In order to reach above-mentioned requirements, the combination of MIMO technology and OFDM technology is also suggested, first using one of core technology as next generation wireless communication technology in 4G technology.MIMO technology and OFDM technology are that two severe challenges of future wireless system---the availability of frequency spectrum and information transmission reliability provide possible solution.(1) OFDM technology is keeping higher transmission rate, the raising availability of frequency spectrum, spread bandwidth and is overcoming in multipath fading have very large advantage; (2) MIMO technology then utilizes the combined coding of many dual-mode antennas to obtain diversity gain raising communication quality, increases channel capacity by spatial reuse.
In order to realize high-throughput, in new generation of wireless communication system, dual-mode antenna number can reach 4 ~ 8, and the highest employing 256QAM modulates, and environmentally can also require the modulation system that adaptive use is different simultaneously.For the quality of a communication system, its quality depends on the accuracy of signal to a great extent, and therefore seeming at the signal detection technique of MIMO-OFDM system receiving terminal is even more important.In MIMO-OFDM system, the model of Received signal strength can be expressed as: Y
k=H
kx
k+ W
k, wherein, Y
krepresent that receiving terminal receives the sub stream signals on a kth subcarrier, X
kfor the primary signal on the kth subcarrier that transmission antennas transmit is come, H
kfor from transmitting terminal to a receiving terminal kth subcarrier corresponding channel response matrix, W
kfor the interference noise on a kth subcarrier.The object of input is exactly the signal Y from receiving
kin recover transmitting data X
k.
It should be noted that, the transmitting-receiving process due to each subcarrier possesses the form of MIMO signal, so by Y
k=H
kx
k+ W
kreferred to as Y=HX+W.Accordingly, Y is represented respectively with Y, X, H and W
k, X
k, H
kand W
k.
What generally adopt in current MIMO-OFDM System on Chip/SoC is linearity test, can meet for early stage requirement.But along with the increase of order of modulation and antenna amount, non-linear detection has become better selection, relatively more conventional had K-best to detect and the sub-optimal detection algorithm such as QRD-M detection, and its performance is close to optimal detection-Maximum Likelihood Detection.But they realize or the problem having complexity higher under parallel programmable structure: their selection constellation, process calculates, and eliminates three steps and data flow can be caused irregular.But BSS-EFE algorithm possesses the advantage of SSFE algorithm on the basis of improving SSFE algorithm performance: not only succinct much in algorithm routine simultaneously, and it is little to the detection computations amount variable quantity of each subcarrier, ensure that the stability of system, be highly suitable in parallel programmable structure and realize.
BSS-EFE algorithm has good performance in high order modulation, also will be highly suitable for 256QAM, but for its poor-performing of low-order-modulated.
Summary of the invention
The present invention is for overcoming at least one defect (deficiency) described in above-mentioned prior art, first a kind of high-performance is provided and is easy to the detection method based on MIMO-OFDM system that realizes in parallel programmable structure, this detection method uses different detection algorithms under different modulating mode, solves and realize the balanced of feasibility and performance.
Another object of the present invention proposes a kind of checkout gear based on MIMO-OFDM system.
For solving the problems of the technologies described above, technical scheme of the present invention is as follows:
Based on a detection method for MIMO-OFDM system, wherein said system comprises: the OFDM baseband system adapting to Different Modulations, and FFT counts as L, total total K subcarrier, L/2<K≤L; Comprise the MIMO receive-transmit system of M root transmitting antenna and N root reception antenna, wherein M≤N; Described method comprises the following steps:
The modulation system of each sub stream signals received by (a) identification;
B () belongs to high-order modulating when described sub stream signals, then adopt the first detection algorithm to detect this subflow, and described high-order modulating refers to the quadrature amplitude modulation of 64 kinds of symbols and the quadrature amplitude modulation of 16 kinds of symbols, i.e. 64QAM and 16QAM; When the signal of described subflow belongs to low-order-modulated mode, then adopt the second detection algorithm to detect this subflow, described low-order-modulated mode comprises Quadrature Phase Shift Keying QPSK and binary phase shift keying BPSK;
Wherein the first detection algorithm is be applicable to high order modulation signal detect and the algorithm that can realize in parallel programmable structure; Second detection algorithm is the algorithm being applicable to low-order-modulated input.
Preferably, described first detection algorithm is BSS-EFE detection algorithm, and the second detection algorithm is direct enumeration.
Preferably, in described step (a), judge the speed of sub stream signals according to field in receiving symbol, determine according to described speed the modulation system that this reception sub stream signals adopts.
Preferably, in the mimo system of 802.11a agreement, judge that the modulation system of signal be currently received is: according to the content of 4 bits before in the signal field of receiving symbol, judge now speed according to described content, determine according to described speed the modulation system that this reception sub stream signals adopts;
In 802.11n agreement, there are three kinds of frame formats, when applying the first form NON-HT, judge the mode of current modulation mode according to the content of 4 bits before in the signal field of receiving symbol; When adopting the second form HT-MF and the third HT-GF, judged the mode of current modulation mode by the bit judging in the HT-SIG1 in signal territory.
In 802.11ac agreement, also there is corresponding field to judge its speed, describe in detail no longer one by one at this.
Preferably, when mimo system or middle the first form of 802.11n protocol application NON-HT of 802.11a agreement, according to the content obtaining modulation intelligence of 4 bit R1-R4 before in the signal field of receiving symbol, concrete mode is:
Described R1-R4 content is 1101 or 1111, and corresponding speed is 6 or 9, then the modulation system that current reception sub stream signals adopts is BPSK;
Described R1-R4 content is 0101 or 0111, and corresponding speed is 12 or 18, then the modulation system that current reception sub stream signals adopts is QPSK;
Described R1-R4 content is 1001 or 1011, and corresponding speed is 24 or 36, then the modulation system that current reception sub stream signals adopts is 16QAM;
Described R1-R4 content is 0001 or 0011, and corresponding speed is 48 or 54, then the modulation system that current reception sub stream signals adopts is 64QAM;
Wherein, described rate unit is Mbit/s.
In 802.11n agreement, have three kinds of frame formats, when applying the first form NON-HT, decision procedure is identical with 802.11a agreement; When adopting the second form HT-MF and the third HT-GF, by judging that the bit in the HT-SIG1 in signal territory carrys out the mode of judgement current modulation mode.Here due to 802.11ac agreement situation too complexity describe in detail no longer one by one.
Based on a checkout gear for MIMO-OFDM system, wherein said system comprises: the OFDM baseband system adapting to Different Modulations, and FFT counts as L, total total K subcarrier, L/2<K≤L; Comprise the MIMO receive-transmit system of M root transmitting antenna and N root reception antenna, wherein M≤N; Signal supervisory instrument comprises:
Receiver module, for receiving each sub stream signals and being estimated the channel response matrix that obtains by channel estimation module;
Identification module, for identifying the modulation system of the sub stream signals received;
Select module, for selecting different detection methods respectively for different modulation systems;
Detection module, for the selection result according to described selected cell, high-order modulating is belonged at described sub stream signals, the first detection algorithm is then adopted to detect this subflow, described high-order modulating refers to the quadrature amplitude modulation of 64 kinds of symbols and the quadrature amplitude modulation of 16 kinds of symbols, i.e. 64QAM and 16QAM; Belong to low-order-modulated mode at the signal of described subflow, then adopt the second detection algorithm to detect this subflow, described low-order-modulated mode comprises Quadrature Phase Shift Keying QPSK and binary phase shift keying BPSK;
Wherein the first detection algorithm is be applicable to high order modulation signal detect and the algorithm that can realize in parallel programmable structure; Second detection algorithm is the algorithm being applicable to low-order-modulated input.
Preferably, described first detection algorithm is BSS-EFE detection algorithm, and the second detection algorithm is direct enumeration.
Preferably, described identification module judges the speed of sub stream signals according to field in receiving symbol, determines according to described speed the modulation system that this reception sub stream signals adopts.
Preferably, in the mimo system of 802.11a agreement, judge that the modulation system of signal be currently received is: according to the content of 4 bits before in the signal field of receiving symbol, judge now speed according to described content, determine according to described speed the modulation system that this reception sub stream signals adopts;
In 802.11n agreement, there are three kinds of frame formats, when applying the first form NON-HT, judge the mode of current modulation mode according to the content of 4 bits before in the signal field of receiving symbol; When adopting the second form HT-MF and the third HT-GF, judged the mode of current modulation mode by the bit judging in the HT-SIG1 in signal territory.
Preferably, described detection module comprises sequencing unit, resolving cell, estimation unit, expanding element and decision unit,
Sequencing unit, the channel response matrix obtained to the received signal and by channel estimating unit sorts;
Resolving cell, carries out QR decomposition by the described channel response matrix through sequence, according to decomposition texture, if R is upper triangular determinant after described decomposition, then from orlop signal, calculates most probable transmission symbol; If R is lower triangular determinant after described decomposition, then from the superiors, calculate the transmission symbol of maximum probability;
Estimation unit, according to the QR decomposition result of described resolving cell to channel matrix H, sends symbol to maximum probability on antenna successively and estimates, and correspond on planisphere;
Expanding element, provides transmission symbols all on every root antenna according to the first described detection algorithm or the second detection algorithm, stores all situations;
Decision unit, according in described estimation unit so result, therefrom rule out the strategic vector of shortest path as Output rusults.
In order to improve the performance of detection algorithm, first some interference are deleted, then first to the received signal and the channel response matrix obtained by channel estimation module sort, to ensure the signal preferentially detecting that reliability is strong, thus reduce the possibility of error code diffusion, finally reach first described in lifting and detect the effect with the performance of the second detection algorithm.
Compared with prior art, beneficial effect of the present invention is:
The present invention adopts the first detection algorithm for the reception sub stream signals of high order modulation; Reception sub stream signals for low-order-modulated adopts the second detection algorithm, and wherein, the first detection algorithm selects amount of calculation little, and program is simple, is adapted at the BSS-EFE algorithm that parallel programmable structure realizes; And for the first detection algorithm in the higher defect of the error rate of low-order-modulated, adopt the second detection algorithm to low-order-modulated, the second detection algorithm is the improvement of the first detection algorithm.Meanwhile, all first channel response matrix and the signal received are sorted before any one algorithm in execution two kinds, ensure the signal that first detecting reliability is strong.The present invention can the signal of any modulation system of adaptive detection, achieves the balanced of realizability and detection perform simultaneously.
Accompanying drawing explanation
Fig. 1 is MIMO-OFDM system principle schematic diagram according to an embodiment of the invention.
Fig. 2 is the signal detecting method flow chart of MIMO-OFDM system according to an embodiment of the invention.
Fig. 3 is the block diagram of the signal supervisory instrument of MIMO-OFDM system according to an embodiment of the invention.
Fig. 4 is the structure chart of detection module in the signal supervisory instrument of MIMO-OFDM system according to an embodiment of the invention.
Fig. 5 is the derivation example schematic of detection module second detection algorithm in the signal supervisory instrument of MIMO-OFDM system according to an embodiment of the invention.
Embodiment
Below in conjunction with the accompanying drawing in the embodiment of the present invention, carry out detailed description to the technical scheme in the embodiment of the present invention, those skilled in the art can understand other advantage of the present invention and effect easily by content disclosed in the present specification.The present invention also can be implemented by other different instantiation application of living, be to be understood that, drawings and the embodiments of the present invention are only for exemplary effect, every details of this specification also based on different viewpoints and application, further can optimized under spirit of the present invention.
Embodiments provide a kind of detection method and receiving system of the multi-input multi-output system based on OFDM, hard-wired complexity can be reduced under the prerequisite ensureing detection perform.
Fig. 1 is MIMO-OFDM system principle schematic diagram according to an embodiment of the invention.Signal sends multiple transmission signal through M root transmitting antenna after OFDM Base-Band Processing, is received, thus obtain corresponding multiple Received signal strength through wireless channel transmission by N root reception antenna.
The model of the Received signal strength of MIMO-OFDM system can simply be expressed as:
Y＝HX+W (1)
Wherein, Y represents the reception sub stream signals of receiving terminal, and X is the primary signal that transmission antennas transmit is come, and H is the channel response matrix from transmitting terminal to receiving terminal, and W is interference noise.
Wherein, Y and W is the column vector of N dimension, and X is the column vector of M dimension, and H is the matrix of the capable N row of M.
Fig. 2 is the signal detecting method flow chart of MIMO-OFDM system according to an embodiment of the invention.As shown in Figure 2, detection method of the present invention comprises the steps:
Step 101, identifies the modulation system of the sub stream signals received;
Specifically, the information of the particular bit position of field that specifies of the agreement used according to system can judge current demand signal speed, thus conclude the modulation system that the signal be currently received uses.
Whether step 102, according to the recognition result of step 101, distinguish the signal of high order modulation and low-order-modulated signal, be namely high order modulation, if yes then enter step 103, otherwise enter step 104;
Specifically, because current ofdm system generally can adopt 64QAM, 16QAM, QPSK, BPSK tetra-kinds of modulation systems respectively, and BSS-EFE detection algorithm possesses good performance in 64QAM and 16QAM two kinds of modulation systems, but there is certain defect in all the other several modulation.So we define 64QAM and 16QAM is here high order modulation, other two kinds are all defaulted as low-order-modulated mode.
Step 103, adopt the first detection algorithm to detect to the sub stream signals received, wherein the first detection algorithm possesses good detection perform in high order modulation signal, and the first detection algorithm is very applicable to hardware implementing.
Step 104, adopts the second detection algorithm to detect to the sub stream signals received, and wherein the second detection algorithm is the improvement that the deficiency existed in low-order-modulated input for the first detection algorithm is carried out.
Fig. 3 is the block diagram of the signal supervisory instrument of MIMO-OFDM system according to an embodiment of the invention.As shown in Figure 3, signal supervisory instrument of the present invention comprises with lower module:
Receiver module 201, for receiving and storing the sub stream signals Y of receiving terminal, and the channel response matrix H estimated by channel estimation module.And described reception sub stream signals Y and channel matrix H are sent to identification module 202 and detection module 204 respectively;
Identification module 202, for identifying the modulation system of the sub stream signals received.Concrete recognition methods is determined according to the particular bit position information in the field specified in the agreement of current use;
Select module 203, according to the recognition result of identification module 202, select different detection methods respectively;
Detection module 204, for the selection result according to selection module 203, the signal being identified as high order modulation at described sub stream signals is applied the first detection algorithm and is detected this subflow, and the signal being identified as low-order-modulated at described sub stream signals is applied the second detection algorithm and detected this subflow;
Wherein, the first described detection algorithm adopts the BSS-EFE algorithm being applicable to high order modulation, and the second detection algorithm is the improvement that the deficiency existed in low-order-modulated for the first detection algorithm is carried out.Due to the sub stream signals of different modulating mode received according to receiving terminal, have employed different algorithms, make use of the first detection algorithm and the second detection algorithm is easy to hard-wired feature, reach the better compromise of performance and complexity.
In addition, each module in present embodiment is logic module, in actual applications, can have various different Physical realization.
Fig. 4 is the structure chart of detection module in the signal supervisory instrument of MIMO-OFDM system according to an embodiment of the invention.Detection module of the present invention comprises with lower unit:
Sequencing unit 301, in order to reduce the error propagation of algorithm, this unit is respectively to channel response matrix with receive sub stream signals and sort, to ensure preferentially the most reliable signal to be detected.Wherein, sort method is as follows:
First the square value of the norm of each column vector of channel response matrix H is sorted, then adjust the column vector of channel response matrix H respectively according to this order and receive the order of sub stream signals column vector Y;
The principle of sequence: reception antenna total mean power
P
n＝|h
1n|
2·E|x
n|
2+|h
2n|
2·E|x
n|
2+.......+|h
Mn|
2·E|x
n|
2
＝(|h
1n|
2+|h
2n|
2+......+|h
Mn|
2)·E|x
n|
2
＝|H
n|
2·E|x
n|
2(2)
As can be seen from formula (2), reception antenna total mean power P
nwhat equal the n-th row column vector norm of channel transfer matrices H square sends the product of average power signal with n-th layer, the average power that ordinary circumstance every layer sends signal is constant, if so arrange sequence and Received signal strength Y line ordering to channel response matrix H respectively according to the order of the square value of the column vector norm of channel response matrix H, the signal priority with maximum signal to noise ratio (the most reliable) can be made to detect, so just can reduce error propagation, improve the performance of whole detection algorithm.
Resolving cell 302, generally reception antenna number N can be more than or equal to number of transmit antennas M, and such guarantee channel response matrix can carry out QR decomposition;
Channel response matrix H, according to the ordering scenario of sequencing unit to channel response matrix H and Received signal strength Y, is resolved into a unitary matrice Q and upper triangular matrix (sequence is by order from small to large) or lower triangular matrix (order of pressing from big to small of sequence) by this unit.
Estimation unit 303, this unit adopts limitary selectivity expanding policy (BSS) to judge the constellation point of the most probable transmitting of each root transmitting antenna, and the constellation point number m of setting expansion flexibly
i(i represents i-th transmitting antenna), 1≤m
i≤ C, (i=N, N-1 ..., 1), C is the constellation number that modulation system determines.Concrete steps are as follows:
H=QR is introduced in Maximum Likelihood Detection, here for M=N, so have:
Wherein,
Will
launch, then obtain:
Can find out from above-mentioned derivation and to decompose through the QR of resolving cell 302, by the method for interference delete, successively up can detect from bottom antenna.BSS strategy is exactly first transport the transmission signal vector ε tentatively determined in this way on every transmit antennas, here referred to as [ε
n... ε
i... ε
1]
t.
Then obtained apart from each ε by the operation that rounds up
iconstellation point within the scope of nearest planisphere.Obtain most probable transmission symbolic vector on every root reception antenna, be designated as
here
represent the n-th alternative constellation point on m transmit antennas.And set decision vector m=(m
n, m
n-1..., m
1).Wherein, 1≤m
i≤ C, (i=N, N-1 ..., 1).M
irepresent possible all constellation point numbers on i-th antenna, work as m
iduring close to constellation point number, mean and carry out deep search to the transmission symbol of antenna, amount of calculation is large, works as m
iduring much smaller than constellation point number, mean coarse search.Amount of calculation and m
isize be directly proportional.
Expanding element 304 is the expansions according to estimation unit 303, the constellation point of the estimation on every root antenna being carried out to most probable constellation point by decision vector to it.The first expanding element 305 or the second expanding element 306 is selected respectively according to the selection information of described selection module 203.
It is to be understood that estimation unit 303 and the first expanding element 305 are collectively referred to as the first detecting unit, estimation unit 303 and the second expanding element 306 are collectively referred to as the second detecting unit.Here be to reduce the complexity that realizes and hardware spending by the object that estimation unit 303 and the first expanding element 305 share a unit.
When the selection of described selection module 203 adopts the first detection algorithm, extended method selects the first expanding element 305 to adopt the expanding policy in BSS-EFE to expand most probable constellation point to adopting the Received signal strength of 64QAM or 16QAM modulation system, and the EFE strategy in BSS-EFE algorithm adopts correlation formula to provide ε
iaround one group nearest
in fact, the method for EFE policy calculation constellation point is that mode that is efficient, that inspire calculates one by one.Require to expand remaining m by decision vector
i-1 most possible constellation point.
The BSS-EFE algorithm that first expanding element 305 uses is the innovatory algorithm easily increasing the proposition of error rate defect for SSFE algorithm in the expansion of constellation point place, border.
When the selection of described selection module 203 adopts the second detection algorithm, extended method selects the second expanding element 306 directly to enumerate (DE) method to may constellation point expand to adopting the Received signal strength of QPSK or BPSK two kinds of modulation systems to adopt.Because the institute on the planisphere of these two kinds of modulation systems is somewhat equal on border, so directly provide ε in the mode directly enumerating (DE)
iconstellation point around, can ensure the stability of algorithm detection perform.
Under QPSK modulation, have 4 constellation point.Below by the process of for example bright enumerative technique;
Fig. 5 enumerates second point principle schematic, wherein d under QPSK modulation system
1=| I (d) |, d
2=| R (d) |,
by comparing d1 and d2, m can be obtained
idirect enumerated table when equaling 2 and 3 is as follows:
Table 1 QPSK modulates m
i=2 (two constellation point) are directly enumerated
| P 1 | d2>d1 | d2≤d1 |
| P 1＝1+j | P 2＝-1+j | P 2＝1-j |
| P 1＝-1+j | P 2＝1+j | P 2＝-1-j |
| P 1＝-1-j | P 2＝1-j | P 2＝-1+j |
| P 1＝1-j | P 2＝-1-j | P 2＝1+j |
Table 2 QPSK modulates m
i=3 (two constellation point) are directly enumerated
| P 1 | P 2,P 3 |
| P 1＝1+j | P 1＝-1+j,P 3＝1-j |
| P 1＝-1+j | P 2＝1+j,P 3＝-1-j |
[0099]
| P 1＝-1-j | P 2＝1-j,P 3＝-1+j |
| P 1＝1-j | P 2＝-1-j,P 3＝1+j |
Work as m
iwhen=4, directly enumerate 4 constellation point, this algorithm just becomes maximal possibility estimation in this case.
Under BPSK modulation, only have two constellation point in planisphere, so only a constellation point need be obtained by estimation unit 303, if also another constellation point can be listed by the second expanding element 306 mode of directly enumerating to improve performance.
Decision unit 307, the effect of this unit is in all paths, find shortest path one group
as final output vector.Wherein
refer to that point on N root antenna in shortest path.
The corresponding same or analogous parts of same or analogous label;
Describe in accompanying drawing position relationship for only for exemplary illustration, the restriction to this patent can not be interpreted as;
Obviously, the above embodiment of the present invention is only for example of the present invention is clearly described, and is not the restriction to embodiments of the present invention.For those of ordinary skill in the field, can also make other changes in different forms on the basis of the above description.Here exhaustive without the need to also giving all execution modes.All any amendments done within the spirit and principles in the present invention, equivalent to replace and improvement etc., within the protection range that all should be included in the claims in the present invention.
Claims (10)
1. based on a detection method for MIMO-OFDM system, wherein said system comprises: the OFDM baseband system adapting to Different Modulations, and FFT counts as L, total total K subcarrier, L/2<K≤L; Comprise the MIMO receive-transmit system of M root transmitting antenna and N root reception antenna, wherein M≤N; It is characterized in that, described method comprises the following steps:
The modulation system of each sub stream signals received by (a) identification;
B () belongs to high-order modulating when described sub stream signals, then adopt the first detection algorithm to detect this subflow, and described high-order modulating refers to the quadrature amplitude modulation of 64 kinds of symbols and the quadrature amplitude modulation of 16 kinds of symbols, i.e. 64QAM and 16QAM; When the signal of described subflow belongs to low-order-modulated mode, then adopt the second detection algorithm to detect this subflow, described low-order-modulated mode comprises Quadrature Phase Shift Keying QPSK and binary phase shift keying BPSK;
Wherein the first detection algorithm is be applicable to high order modulation signal detect and the algorithm that can realize in parallel programmable structure; Second detection algorithm is the algorithm being applicable to low-order-modulated input.
2. the detection method based on MIMO-OFDM system according to claim 1, is characterized in that, described first detection algorithm is BSS-EFE detection algorithm, and the second detection algorithm is direct enumeration.
3. the detection method based on MIMO-OFDM system according to claim 1 and 2, it is characterized in that, in described step (a), judge the speed of sub stream signals according to field in receiving symbol, determine according to described speed the modulation system that this reception sub stream signals adopts.
4. the detection method based on MIMO-OFDM system according to claim 3, it is characterized in that, in the mimo system of 802.11a agreement, judge that the modulation system of signal be currently received is: according to the content of 4 bits before in the signal field of receiving symbol, judge now speed according to described content, determine according to described speed the modulation system that this reception sub stream signals adopts;
In 802.11n agreement, there are three kinds of frame formats, when applying the first form NON-HT, judge the mode of current modulation mode according to the content of 4 bits before in the signal field of receiving symbol; When adopting the second form HT-MF and the third HT-GF, judged the mode of current modulation mode by the bit judging in the HT-SIG1 in signal territory.
5. the detection method based on MIMO-OFDM system according to claim 4, it is characterized in that, when mimo system or middle the first form of 802.11n protocol application NON-HT of 802.11a agreement, according to the content obtaining modulation intelligence of 4 bit R1-R4 before in the signal field of receiving symbol, concrete mode is:
Described R1-R4 content is 1101 or 1111, and corresponding speed is 6 or 9, then the modulation system that current reception sub stream signals adopts is BPSK;
Described R1-R4 content is 0101 or 0111, and corresponding speed is 12 or 18, then the modulation system that current reception sub stream signals adopts is QPSK;
Described R1-R4 content is 1001 or 1011, and corresponding speed is 24 or 36, then the modulation system that current reception sub stream signals adopts is 16QAM;
Described R1-R4 content is 0001 or 0011, and corresponding speed is 48 or 54, then the modulation system that current reception sub stream signals adopts is 64QAM;
Wherein, described rate unit is Mbit/s.
6. based on a checkout gear for MIMO-OFDM system, wherein said system comprises: the OFDM baseband system adapting to Different Modulations, and FFT counts as L, total total K subcarrier, L/2<K≤L; Comprise the MIMO receive-transmit system of M root transmitting antenna and N root reception antenna, wherein M≤N; It is characterized in that, comprising:
Receiver module, for receiving each sub stream signals and being estimated the channel response matrix that obtains by channel estimation module;
Identification module, for identifying the modulation system of the sub stream signals received;
Select module, for selecting different detection methods respectively for different modulation systems;
Detection module, for the selection result according to described selected cell, high-order modulating is belonged at described sub stream signals, the first detection algorithm is then adopted to detect this subflow, described high-order modulating refers to the quadrature amplitude modulation of 64 kinds of symbols and the quadrature amplitude modulation of 16 kinds of symbols, i.e. 64QAM and 16QAM; Belong to low-order-modulated mode at the signal of described subflow, then adopt the second detection algorithm to detect this subflow, described low-order-modulated mode comprises Quadrature Phase Shift Keying QPSK and binary phase shift keying BPSK;
Wherein the first detection algorithm is be applicable to high order modulation signal detect and the algorithm that can realize in parallel programmable structure; Second detection algorithm is the algorithm being applicable to low-order-modulated input.
7. the checkout gear based on MIMO-OFDM system according to claim 6, is characterized in that, described first detection algorithm is BSS-EFE detection algorithm, and the second detection algorithm is direct enumeration.
8. the checkout gear based on MIMO-OFDM system according to claim 6 or 7, it is characterized in that, described identification module judges the speed of sub stream signals according to field in receiving symbol, determines according to described speed the modulation system that this reception sub stream signals adopts.
9. the checkout gear based on MIMO-OFDM system according to claim 8, it is characterized in that, in the mimo system of 802.11a agreement, judge that the modulation system of signal be currently received is: according to the content of 4 bits before in the signal field of receiving symbol, judge now speed according to described content, determine according to described speed the modulation system that this reception sub stream signals adopts;
In 802.11n agreement, there are three kinds of frame formats, when applying the first form NON-HT, judge the mode of current modulation mode according to the content of 4 bits before in the signal field of receiving symbol; When adopting the second form HT-MF and the third HT-GF, judged the mode of current modulation mode by the bit judging in the HT-SIG1 in signal territory.
10. the checkout gear based on MIMO-OFDM system according to claim 9, is characterized in that, described detection module comprises sequencing unit, resolving cell, estimation unit, expanding element and decision unit,
Sequencing unit, the channel response matrix obtained to the received signal and by channel estimating unit sorts;
Resolving cell, carries out QR decomposition by the described channel response matrix through sequence, according to decomposition texture, if R is upper triangular determinant after described decomposition, then from orlop signal, calculates most probable transmission symbol; If R is lower triangular determinant after described decomposition, then from the superiors, calculate the transmission symbol of maximum probability;
Estimation unit, according to the QR decomposition result of described resolving cell to channel matrix H, sends symbol to maximum probability on antenna successively and estimates, and correspond on planisphere;
Expanding element, provides transmission symbols all on every root antenna according to the first described detection algorithm or the second detection algorithm, stores all situations;
Decision unit, according in described estimation unit so result, therefrom rule out the strategic vector of shortest path as Output rusults.
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