CN103986328A - DC-DC converters having improved current sensing and related methods - Google Patents

DC-DC converters having improved current sensing and related methods Download PDF

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Publication number
CN103986328A
CN103986328A CN201410240027.8A CN201410240027A CN103986328A CN 103986328 A CN103986328 A CN 103986328A CN 201410240027 A CN201410240027 A CN 201410240027A CN 103986328 A CN103986328 A CN 103986328A
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current
electric current
resistance
coupled
circuit
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R·H·艾沙姆
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Intersil Corp
Intersil Americas LLC
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Intersil Inc
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Abstract

A DC-DC converter includes a chip including an error amplifier and a pulse width modulator (PWM) having an input connected to an output of the error amplifier, and an inductor driven by said PWM in series with an output node (VOUT) of the converter, wherein a load current flows through the inductor. VOUT is fed back through a network including a feedback resistor (RFB) to an inverting input of the error amplifier. A circuit for sensing the load current includes a first operational amplifier, a sense resistor on the chip having resistance RSENSE coupled to an inverting input of the first amplifier; wherein a sense current related to the load current flows through the sense resistor, a dependent current source provides an output current to supply the sense current. A reference resistor is disposed on the chip having a resistance RREFERENCE which is a fixed multiple of RSENSE. A set resistor is provided having a resistance RSET. Tracking circuitry sets a voltage across the reference resistor to be equal to a voltage across the set resistor. A function block is coupled to receive a current through the set resistor and a current through the reference resistor to find their ratio. A current multiplier is provided, wherein an output of the function block is coupled to the current multiplier. The current multiplier provides a measurement current which is proportional to the load current divided by RSET.

Description

There is the DC-DC converter and the correlation technique that improve electric current induction
The application be applicant on October 23rd, 2006 submit to, application number is " 200610136584.0 ", denomination of invention divides an application for " having the DC-DC converter and the correlation technique that improve electric current induction " and the application for a patent for invention that is " 201110128753.7 " in the application number that on May 10th, 2011 submits to, denomination of invention is " having the DC-DC converter and the correlation technique that improve electric current induction ".
Related application the present invention requires in the priority of the provisional application No.60/808197 that is entitled as " METHOD OF IMPROVED CURRENT SENSING IN DC-DC CONVERTERS " of submission on May 24th, 2006, and the full content of this application is incorporated herein by reference.
Technical field
The present invention relates to the accurate measurement of inductive current, be particularly useful for controlling the switch in voltage regulator circuit and related power circuit.
Background technology
Accurately sensing lead electric current is so that realize the control of the various device that comprises current motor, DC-DC converter circuit and voltage regulator circuit.A kind of well-known circuit 100 for the inductive current sensing lead electric current by stream DC-DC converter is shown in Fig. 1 (a).Pin in circuit 100 with between the part on vertical dotted line right side conventionally in the inside of IC chip, and conventionally in comprising of IC chip exterior, contain inductor L110 and C fILTERthe part of the low pass filter of (output capacitor) exists with between the left side of dotted line.There is inductance L and there is external inductance L110 and the C of DC resistance DCR fILTERform a part for low-pass filter network, this C fILTERthe input signal of the apply pulse width modulated that will be provided by pulse-width modulator (PWM, not shown) converts load R to lOADon steady state voltage output V oUT.A part for the upper voltage drop of L110 is that the DC resistance that is shown DCR by it causes.Resistance R with capacitor's series iNDwith capacitor C iNDbe illustrated as being placed on inductor 110, thus R iND/ C iNDthe time constant of closely mating with the time constant of L/DCR is provided.
C iNDon across voltage, in Fig. 1 (a), be shown V iND, the voltage drop on coupling DCR, and thereby as inductive current I iNDeffective indication.Operational amplifier A 1 is placed in circuit 100, and with the grid of driving N mos transistor Q1, the source electrode of transistor Q1 is at pin place connects back the inverting input of A1.Inductive reactance R sENSE120 are placed in pin with V oUTbetween.
Be connected in pin the homophase input of A1 be connected to R iNDwith C iNDbetween node.In this configuration, the high-gain of A1 is by pin voltage be driven into and equal in fact pin voltage, thereby capacitor C iNDon equal V iNDvoltage will be placed in R sENSEon.Then Q1 equals transmission to V iND/ R sENSE, or I iND* DCR/R sENSEelectric current.This electric current I sENSEcan obtain in the drain electrode of Q1, and follow I oUTcan process and for overcurrent release or for arranging through adjusting output impedance.
Although Q1 is illustrated as Nmos transistor in Fig. 1, in optional embodiment, also its drain current combines to form the Nmos of bidirectional current induction and the combination of Pmos.Also can be only being that bias current exists increase and at I oUTreduce back initial value to allow Nmos or the Pmos of bidirectional current induction.
R sENSEresistance with pin also can connect on synchronous rectifier FET.In the case, the RDS of FET oNit can be the current sensing elements that substitutes inductor DCR.By MOSFET r under sampling when PWM drives synchronous rectifier dS (ON)on the load current induction of voltage shown in the circuit 140 shown in Fig. 1 (b).PWM150 driving grid driver 152, this gate drivers 152 drives upper and lower (synchronous rectifier) two to drive in turn the Nmos156 and 157 of inductor 160.Amplifier A1 is by ISEN-output being connected to the ground connection benchmark of the source electrode of MOSFET157.When FET156 conducting, inductive current I lfrom V iNflow through 156, and during FET157 conducting instantly, from earth terminal, flow out.Inductive current (I l) therefore make the pressure drop on FET157 equal RDS oNwith the product of inductive current, the resistance of this inductive current and inductive reactance 170 is multiplied by sensed electric current (I sEN) relevant.Particularly, enter I sEN+the result electric current of pin and channel current I lproportional.Then I sENelectric current is fully being sampled and is keeping after setting time, as well known in the field in this technique.Sample rate current can be used for comprising in the application of channel current balance, loaded line adjustment and overcurrent protection.
R in circuit 100 and 140 sENSEbeing provided in chip is outward because R sENSEneed to be adjustable, thereby obtain the expectation I for circuit 100 oUTvalue is for DCR and I iNDvarious combination.For example,, if I oUTcompare to produce overcurrent release with the fixed current value that integrated circuit (IC) is inner, and inductor DCR and desired I iNDcurrent-release point arranges by system restriction, R sENSEvalue must be adjusted to expect I iNDupper acquisition expectation I oUT.Because need the cause of adjustability, so R sENSEconventionally be arranged on as shown in Figure 1 the outside of IC.R sENSEconventionally second reason that is arranged on IC outside is that most of integrated circuit technologies are not supported accurate and stable internal resistor.
Use outside R sENSEa problem be I sENSE+the susceptibility of pin to the noise jamming as shown in Fig. 1 (a) and 1 (b), this noise jamming is the noise being coupled by capacitor parasitics 130.Refer again to Fig. 1 (a), be capacitively coupled to pin I sENSE+noise current be revealed as the drain current of the Q1 that comprises noise component(s) shown in Fig. 1, be I oUT+Noise.Known this noise coupling can have a negative impact to performance, and has required very meticulous printed circuit board wiring to minimize pin I sENSE+on capacitive coupling.Conventionally attempt I sENSE+it is infeasible being set as bypass, dispose into a limit, thereby may make A1 unstable because this understands in the feedback of amplifier A1.
Thereby, need to be through improved switching regulation circuit, particularly be used in the current measurement circuit of accurate sensing lead electric current in switching regulation circuit, circuit for controlling motor etc., they need to not have outside accurate R on the inverting input of A1 with additional noise susceptibility sENSE.
Summary of the invention
DC-DC converter comprises: the chip that includes the pulse-width modulator (PWM) that error amplifier and input be connected to error amplifier output; By the output node (V with this converter oUT) inductor that the described PWM of series connection drives, wherein load current flows through inductor.V oUTby comprising that the network-feedback of feedback resistance (RFB) is to the inverting input of error amplifier.Circuit for inductive load current comprises: the first operational amplifier; On chip, there is resistance R sENSEthe inductive reactance of the inverting input that is coupled to the first amplifier; The induced current that is wherein relevant to load current flows through inductive reactance, and correlated current source provides output current with supply induced current.Reference resistance is arranged on chip and has the R of being sENSEthe fixing resistance R of multiple rEFERENCE.Set resistance and be arranged to there is resistance R sET.Tracking circuit is arranged to equal to set ohmically voltage by the voltage on reference resistance.Functional block is coupled to receive by setting the electric current of resistance and obtaining their ratio by the electric current of reference resistance.Electric current multiplier is configured to the wherein output of functional block and is connected to this electric current multiplier.Electric current multiplier provides with load current divided by R sETproportional measurement electric current.
The present invention can utilize the various Circnit Layouts for inductive load current.In one embodiment, use inductor DCR induction, wherein converter also comprises and the resistance of crossing over the capacitor's series of inductor placement, and this resistance has the DC resistance (DCR) that is designed to the time constant matching with the time constant of inductor and is associated.In another embodiment, use MOSFET r dS (ON)induction, wherein converter also comprises and is connected in the output of PWM and the synchronous rectifier between inductor.
Inductive reactance and described reference resistance are preferably manufactured from the same material.In one embodiment, converter comprises current mirror, it has and is connected to the output of error amplifier end of oppisite phase and for the input of measurement of inductance electric current, described current mirror becomes source electric current to flow through RFB described measurement current conversion, improves the electromotive force of the inverting input of described error amplifier control output impedance with the increase along with measurement electric current.In another embodiment, converter also comprises and makes comparisons and produce and apply a reset signal and to prevent PWM, enter the structure of overcurrent condition to PWM measuring electric current and fixed reference electric current.In this embodiment, for structure relatively, can comprise converter, the output of this converter is coupled to the replacement pin of converter, if wherein measure electric current, is greater than reference current, and PWM will be forbidden.
In DC-DC converter, the method for electric current induction comprises the following steps: DC-DC converter chip is provided, it comprises the error amplifier that is coupled to the pulse-width modulator (PWM) that drives inductor, this inductor be suitable for by the output node (V of the converter of load ground connection oUT) series connection, wherein load current flows through described inductor.V oUTvia the network-feedback that comprises feedback resistance (RFB), return the inverting input of error amplifier.Be used for the circuit that comprises inductive reactance of inductive load current at chip, this inductive reactance has for generation of the faradic resistance value (R that is relevant to load current sENSE).Correlated current source provides output current (I oUT) so that induced current to be provided.Reference resistance is arranged on chip and has the R of being sENSEthe fixing resistance R of multiple rEFERENCE.Be provided with and there is resistance R sETsetting resistance, be also provided with for the voltage on reference resistance being arranged to equal to set the tracking circuit of ohmically voltage.
The electric current of setting resistance of flowing through is determined with the ratio of the electric current of the reference resistance of flowing through.Then with described R sENSEthe irrelevant measurement electric current of actual value with this ratio, determine, this measures electric current and load current divided by R sETproportional.
For responding to the circuit of described load current, can realize inductor DCR induction.In another embodiment, for responding to the circuit of described load current, realize MOSFET r dS (ON)induction.
The method also can comprise utilizing measures electric current so that the step of fixedly output impedance to be provided.In this embodiment, this utilizes step to comprise measurement electric current (normally Absorption Current) is transformed into source electric current, and the source electric current of making flows through feedback resistance to increase along with the increase of inductive current on inverting input with respect to V oUTvoltage.
In another embodiment of the present invention, the method is further comprising the steps of: if load current increases to, exceed scheduled volume, utilize measurement electric current to close PWM to avoid PWM to enter overcurrent condition.In this embodiment, this utilizes step to comprise: measurement electric current and predetermined reference current are made comparisons, and if measure electric current, be greater than reference current, be cut to the power supply of described PWM.In one embodiment, measure electric current and reference current and be all configured to input inverter, the output of this inverter is coupled to the replacement pin of adjuster, is greater than reference current, PWM forbidding if wherein measure electric current.
Accompanying drawing explanation
By consulting following detail specifications and accompanying drawing, the present invention with and the complete understanding of feature and advantage can be accomplished, wherein
Fig. 1 (a) is the schematic diagram of realizing the known load electric current induction of inductor DCR induction in DC-DC converter.
Fig. 1 (b) is when PWM drives synchronous rectifier, in DC-DC converter, realizes r dS (ON)the schematic diagram of the known circuit of the load current induction of induction.
Fig. 2 illustrates to be had according to an embodiment of the invention for measuring the circuit of induced inside resistance of the inductive current of DC-DC converter.
Fig. 3 illustrate comprise with inductor DCR according to another embodiment of the present invention, respond to carry out sensing lead electric current, with the schematic diagram of the exemplary DC-DC converter of the circuit of the output impedance of control change device.
Fig. 4 illustrate comprise reuse according to the inductor DCR of further embodiment of this invention, respond to carry out sensing lead electric current, with the schematic diagram of the exemplary DC-DC converter of the circuit of the PWM power supply of overcurrent release action protection converter.
Embodiment
Have according to an embodiment of the invention in realizing the DC-DC converter of inductor DCR induction or other switching regulation circuit for the circuit of the induced inside resistance of load current induction shown in Figure 2.Circuit 200 comprises and circuit element identical in circuit 100 shown in Fig. 1 (a), but added the adjunct circuit 250 (illustrating in dotted line) that comprises benchmark and tracking circuit, this benchmark and tracking circuit make the to flow through inductive current of inductor 110 can have nothing to do in R sENSE120 actual value is measured.The same with circuit 100, circuit 200 comprises the common part in IC inside and common part (inductor L110 and C in IC outside fILTERconventionally outside at IC).Yet, different from circuit shown in Fig. 1 100, R sENSEinner at IC.
Circuit 200 is included in I oUTelectric current multiplier 215 on path is I to form oUTmultiple, equal M*I oUToutput current I oUT2.Circuit 200 arranges the second resistance R in IC inside rEFERENCE220.R rEFERENCE220 owing to being placed in R on chip sENSEnear 120 and by with R sENSE120 identical electric conducting materials are made, so can be manufactured with accurate control and R sENSEresistance ratio K.That is, R rEFERENCE=K*R sENSE.K can be independent of process reform or temperature change obtains, and can be to be greater than or less than arbitrarily 1 convenient value.Circuit 200 also comprises non-essential resistance R sET235.R sETthe voltage of 235 high potential sides is shown to be coupled to V cC, and R sET235 low potential side is driven into any reference voltage.As shown in Figure 2, R sETany reference voltage of 235 low potential sides arranges by comprising the exemplary circuit of voltage source V 1, and this voltage source V 1 is coupled to Pmos source follower Q2.
As in common knowledge in those skilled in the art, the source electrode of MOS transistor can exchange role at transistor duration of work with drain electrode.Therefore, for identifying the term " source electrode " of the current-carrying electrode of MOS transistor, serving as source electrode or draining in being not intended to respect to the special time at circuit working with " drain electrode " and limiting the performed function of current-carrying electrode herein and in claim.
Operational amplifier A 2250 link together to drive R with Pmos Q3255 rEFERENCE220 low potential end, thereby R rEFERENCE220 have in fact and R sET235 identical voltages.R rEFERENCE220 can be by other drives such as NPN/PNP mixing follower, but in application-specific, system accuracy requires to get rid of the method.From R rEFERENCE220 electric current with from R sET235 electric current is fed to functional block F1260.F1 can expand a multiplier multiple M by well-known analog or digital circuit, and this multiple M equals to pass through R sETelectric current with pass through R rEFERENCEthe ratio of electric current.Because be inversely proportional to by thering is electric current and each resistance value of the resistance of same potential on it, so M equals R rEFERENCE/ R sET.Because R rEFERENCEequal K*R sENSEso, M=K*R sENSE/ R sET.
As mentioned above for circuit shown in Fig. 1 100, output current I oUTequal I iND* DCR/R sENSE.I OUT2＝M*I OUT＝M*I IND*DCR/R SENSE。Use K*R sENSE/ R sETsubstitute M:
I OUT2＝K*DCR/R SET(1)
Importantly, in equation (1), there is no R sET, and I oUT2only depend on external circuit elements (L and R sET, and the DC resistance (DCR) of L) value.Therefore, do not require R sENSEaccurate.R sENSE120 relative R of needs rEFERENCEhave fixed ratio (K), this fixed ratio is easy to arrange by circuit design.Because resistance is proportional, so for R sENSEwith R rEFERENCEthe resistivity of electric conducting material in the change of technique (or temperature) can not affect the precision of the current measurement being provided by circuit 200.
Pmos follower (Q2 and Q3) is illustrated as driving R sENSE235 and R rEFERENCE220, and R sENSEwith R rEFERENCEbe illustrated as termination positive supply VCC.Although what illustrate is Pmos follower, driver also may be selected to be the bipolar transistor of NMOS or arbitrary polarity, but and termination ground connection or other power supply.If be presented as nmos drive transistor, drive the voltage reference V1 of Q2 grid to incite somebody to action the suitably reverse of polarity and termination.
Although not shown in Figure 2, R rEFERENCE220 can drive by reference voltage V 1 and follower, and R sETcan effectively be driven by A2 and Q3.This is normally lower than desired, because R sETparasitic capacitance can in the feedback of A2250, produce a limit, this can cause A2 unstable.
Circuit 200 can be used for providing the switching regulation circuit that benefits from the accurate inductive current of measuring through improved, such as DC-DC converter, circuit for controlling motor etc.
Fig. 3 and Fig. 4 show induced current I oUT2exemplary use with respect to the DC-DC converter of pulse width modulation.Fig. 3 has illustrated the output impedance of control change device, and Fig. 4 illustrates use overcurrent release action protection PWM power supply.Yet, noting, the present invention is not limited to the DC-DC converter of pulse width modulation, because it may be used on Other related equipment.In addition, as mentioned above, the load current sensor circuit that is different from the circuit based on inductor DCR induction can be applicable to the present invention.For example, shown in Fig. 1 (b), realize MOSFET r dS (ON)the replaceable use of device of electric current induction, wherein induction connection ( with ) be connected to source electrode and the drain electrode thereof of lower FET (ground connection).Other suitable load current sensor circuit also can be used for the present invention.
Referring now to Fig. 3, the schematic diagram of exemplary PWM DC-DC converter 300 is shown, this converter 300 comprises: for measure the pin of crossing over inductor 110 according to the present invention with the circuit 310 of inductive current, this capacitor CF is formed for the low pass filter of load RL together with inductor 110.Converter 300 comprises error amplifier 350, and this error amplifier 350 is by applied reference voltage V rEFwith through regulation output voltage V oUTmake comparisons.V oUTthrough resistance R FB, feed back to the inverting input of amplifier 350, node FB.Other is coupling in the output node COMP of error amplifier 350 and the compensating element, RC1 between node FB and CC1 is for suitable system responses is provided.Node COMP driving pulse width modulator PWM360, this pulse-width modulator PWM360 arranges some relations between its COMP voltage input and duty cycle output.Input to PWM360 provides the conventional oscillator of clock signal (for example sawtooth waveforms) not to be illustrated.PWM output signal PWM oUTby inductor LF110 and capacitor CF low-pass filter, become output voltage V oUT.It is that adjuster has appointment output impedance that the typical case of DC-DC converter requires.Be V oUTmust be with respect to the load current I increasing lOADwith fixed ratio, reduce to fixing appointment output impedance is provided.
Circuit 310 for inductance measuring electric current is used in the converter 300 shown in Fig. 3, to respond to the electric current by LF110, should be essentially identical electric current with the above-mentioned electric current by load RL on average by the electric current of LF110.For measuring the circuit 310 of electric current, can be presented as circuit 200, this circuit 200 comprises the R that crosses over LF110 iNDwith C iND, V on chip oVOwith r between pin sENSE, and shown in the R shown in circuit 200 sETadd together pin to with other exemplary circuit on right side.
The electric current I being produced by the circuit 310 for inductance measuring electric current oUT2be applied in, and used current mirror and there is suitable polarity.The output of current mirror 330 means as I oUT2source electric current, its RFB that flows through, thus along with I lOADincrease and with respect to V oUTincrease the voltage on node FB.Then error amplifier 350 reduces V oUTvoltage, thereby node FB keeps equaling V rEF, thereby desired fixedly output impedance is provided.
Fig. 4 shows for according to the second exemplary application of inductive current induction circuit of the present invention.Fig. 4 shows the schematic diagram of exemplary PWM DC-DC converter 400, and this PWM DC-DC converter 400 comprises in a circuit according to the invention 310, and this circuit 310, for inductance measuring electric current, is used for overcurrent release action protection PWM power supply.As described in respect to Fig. 3, for measuring the circuit 310 of electric current, can be presented as the exemplary measuring circuit shown in Fig. 2.
When work, if load current I lOADincrease to and surpass scheduled current level, according to the circuit 310 for inductance measuring electric current of the present invention, can cut off the power supply of PWM360.In one embodiment, inverter 435 is coupled to the replacement pin of PWM360.I oUT2with provided fixed reference electric current I rEFmake comparisons.For normal running, require replacement pin for for high converter, if I oUT2be greater than I rEF, the input of inverter 435 will be dragged down, and this will cause inverter to uprise and send reset signal making PWM360 disabled to PWM360, thereby prevent that PWM360 from entering overcurrent condition.
This invention provides some remarkable advantages.An advantage is exactly R sENSEon chip, thereby cause the anti-phase input of A1, be an inner node, and therefore shield the capacitive coupling of noise.In circuit 200 with node is all low-impedance, so be more not easy to be subject to noise jamming.Another advantage is exactly from non-essential resistance R sETinput can be DC or low frequency because it can not affect from I sENSEto I oUT2the bandwidth in path.So R sETcan be set as bypass (by-pass capacitor is not shown) to prevent noise jamming.
Also having an advantage is exactly R sETcan be used to control I sENSEto I oUT2some passages.This with each passage is used to separate outer R sETcompare and can save element.Another advantage is exactly that thermistor can be used to temperature change R sETvalue, and by I oUT2gain adjust to the conductive coefficient of inductor DCR and match.Positive temperature coefficient thermistor (PTC) or PTC-resistor network can be used to replace R sET.PTC or PTC-resistor network may be selected to be has the temperature coefficient identical with the DCR of inductor, and will be placed with and be convenient to heat and follow the tracks of inductor.Along with the increase of inductor temperature and the therefore increase of its DCR value, the constant ratio of given induced current and actual inductive current, the similar resistance value of PTC or PTC-resistor network increases and will reduce the gain amplifier of sensor circuit.Thermistor is set as bypass to prevent noise jamming near IC.
Be understandable that, although combine preferred specific embodiment of the present invention, described the present invention, description above and example below are all intended to explanation but not limit the scope of the invention.Other side in the scope of the invention, advantage and change are apparent for those skilled in the art of the invention.

Claims (10)

1. one kind is configured to be coupled to current sensing elements and resistance value is R setthe integrated circuit of setting resistance, described integrated circuit comprises:
Inductive reactance, its resistance value is R sense, described inductive reactance is coupled to the input of integrated circuit so that flow through described inductive reactance from the first induced current of described current sensing elements;
Reference resistance, has the R of being sensethe resistance value R of fixedly multiple reference; And
Described circuit is configured to produce output current, so that the same R of the value of described output current setvalue and R sensewith R referencefixed ratio proportional.
2. integrated circuit as claimed in claim 1, it is characterized in that, described circuit in described integrated circuit comprises tracking circuit, and described tracking circuit is configured to drive described reference resistance so that the voltage on described reference resistance is substantially equal to the ohmically voltage of described setting.
3. integrated circuit as claimed in claim 2, is characterized in that, described tracking circuit comprises:
Source follower, is coupled to the low potential end of described reference resistance; And
Operational amplifier, has the output of the grid that is coupled to described source follower.
4. integrated circuit as claimed in claim 1, is characterized in that, described reference resistance and described inductive reactance consist of the material of same type.
5. integrated circuit as claimed in claim 1, is characterized in that, the circuit in described integrated circuit is configured to definite R that passes through setelectric current with pass through R referencethe ratio of electric current, and R is passed through in combination setelectric current with pass through R referencethe ratio and first of electric current measure electric current to produce described output current.
6. an integrated circuit, comprising:
First input end, it is configured to be coupled to current sensing elements;
The second input, it is configured to be coupled to the setting resistance with the first resistance value;
The inductive reactance with the second resistance value, described inductive reactance is coupled to described first input end so that voltage is placed across described inductive reactance, to generate the first measurement electric current based on described the second resistance value;
The reference resistance with the 3rd resistance value, described the 3rd resistance value is the fixedly multiple of described the second resistance value; And
Electric current multiplier, it is configured to measure the electric current of electric current and described the second input end and generate the second measurement electric current with the ratio of electric current by described reference resistance by combining described first, and described second measures electric current indication load current and be independent of described the second resistance value.
7. integrated circuit as claimed in claim 6, is characterized in that, also comprises tracking circuit, and described tracking circuit is configured to drive described reference resistance so that the voltage on described reference resistance is substantially equal to the ohmically voltage of described setting.
8. integrated circuit as claimed in claim 7, is characterized in that, described tracking circuit comprises:
Source follower, is coupled to the low potential end of described reference resistance; And
Operational amplifier, has the output of the grid that is coupled to described source follower.
9. integrated circuit as claimed in claim 6, is characterized in that, described reference resistance and described inductive reactance consist of the material of same type.
10. integrated circuit as claimed in claim 6, is characterized in that, also comprises:
Transistor, has grid, source electrode and drain electrode; And
Operational amplifier, its input is coupled to described inductive reactance and output is coupled to described transistorized described grid;
Wherein said transistorized grid is coupled to described electric current multiplier and offers described electric current multiplier to measure electric current by described first.
CN201410240027.8A 2006-05-24 2006-10-23 DC-DC converters having improved current sensing and related methods Pending CN103986328A (en)

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CN102299627A (en) 2011-12-28
TWI404316B (en) 2013-08-01

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Application publication date: 20140813