CN102299627B - DC-DC converters having improved current sensing and related methods - Google Patents
DC-DC converters having improved current sensing and related methods Download PDFInfo
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- CN102299627B CN102299627B CN201110128753.7A CN201110128753A CN102299627B CN 102299627 B CN102299627 B CN 102299627B CN 201110128753 A CN201110128753 A CN 201110128753A CN 102299627 B CN102299627 B CN 102299627B
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Abstract
Provided is a power converter with a set resistor having a resistance RSET. Each of the channels of the power converter include an error amplifier for comparing reference voltage with adjusted output voltage; a pulse width modulator (PWM) for adjusting the output voltage, a current sensing element for sensing a first current, a sense resistor having resistance RSENSE coupled to the current sensing element such that the first current flows through the sense resistor, a reference resistor having a resistance RREFERENCE which is a fixed multiple of RSENSE, and a circuit coupled to a set resistor, the reference resistor and the sense resistor; the circuit is configured to output current; the value of the output current with the RSET is proportional to the RSENSE with the RREFERENCE, wherein the circuit provides output current to the error amplifier.
Description
The application be applicant on October 23rd, 2006 submit to, divisional application that application number is " 200610136584.0 ", that denomination of invention is the application for a patent for invention of " having the DC-DC converter and the correlation technique that improve electric current induction ".
Related application the present invention requires in the priority of the provisional application No.60/808197 that is entitled as " METHOD OF IMPROVED CURRENT SENSING IN DC-DC CONVERTERS " of submission on May 24th, 2006, and the full content of this application is incorporated herein by reference.
Technical field
The present invention relates to the accurate measurement of inductive current, be particularly useful for controlling the switch in voltage regulator circuit and related power circuit.
Background technology
Accurately sensing lead electric current is so that realize the control of the various device that comprises current motor, DC-DC converter circuit and voltage regulator circuit.A kind of well-known circuit 100 for the inductive current sensing lead electric current by flowing into DC-DC converter is shown in Fig. 1 (a).Pin in circuit 100
with
between the part on vertical dotted line right side conventionally in the inside of IC chip, and conventionally contain inductor L 110 and C in comprising of IC chip exterior
fILTERthe part of the low pass filter of (output capacitor) exists
with
between the left side of dotted line.There is inductance L and there is external inductance L 110 and the C of DC resistance DCR
fILTERform a part for low-pass filter network, this C
fILTERthe input signal of the apply pulse width modulated that will be provided by pulse-width modulator (PWM, not shown) converts load R to
lOADon steady state voltage output V
oUT.On L 110, a part for voltage drop is that the DC resistance that is shown DCR by it causes.Resistance R with capacitor's series
iNDwith capacitor C
iNDbe illustrated as being placed on inductor 110, thus R
iND/ C
iNDthe time constant of closely mating with the time constant of L/DCR is provided.
C
iNDon across voltage, in Fig. 1 (a), be shown V
iND, the voltage drop on coupling DCR, and thereby as inductive current I
iNDeffective instruction.Operational amplifier A 1 is placed in circuit 100, and with the grid of driving N mos transistor Q1, the source electrode of transistor Q1 is at pin I
place connects back the inverting input of A1.Inductive reactance R
sENSE120 are placed in pin
with V
oUTbetween.
Be connected in pin
the homophase input of A1 be connected to R
iNDwith C
iNDbetween node.In this configuration, the high-gain of A1 is by pin
voltage be driven into and equal in fact pin
voltage, thereby capacitor C
iNDon equal V
iNDvoltage will be placed in R
sENSEon.Then transmission is equaled V by Q1
iND/ R
sENSE, or I
iND* DCR/R
sENSEelectric current.This electric current I
sENSEcan obtain in the drain electrode of Q1, and follow I
oUTcan process and for overcurrent release or for arrange through adjust output impedance.
Although Q1 is illustrated as Nmos transistor in Fig. 1, in optional embodiment, also its drain current combines to form the Nmos of bidirectional current induction and the combination of Pmos.Also can be only being that bias current exists
increase and at I
oUTreduce back initial value to allow Nmos or the Pmos of bidirectional current induction.
R
sENSEresistance with
pin also can connect on synchronous rectifier FET.In the case, the RDS of FET
oNit can be the current sensing elements that substitutes inductor DCR.By MOSFET r under sampling in the time that PWM drives synchronous rectifier
dS (ON)on the load current of voltage respond to shown in the circuit 140 shown in Fig. 1 (b).PWM 150 driving grid drivers 152, this gate drivers 152 drives upper and lower (synchronous rectifier) two to drive in turn the Nmos 156 and 157 of inductor 160.Amplifier A1 is the ground connection benchmark by ISEN-output being connected to the source electrode of MOSFET 157.In the time of FET 156 conducting, inductive current I
lfrom V
iNflow through 156, and when FET 157 conducting instantly, flow out from earth terminal.Inductive current (I
l) therefore make the pressure drop on FET 157 equal RD
sONwith the product of inductive current, the resistance of this inductive current and inductive reactance 170 is multiplied by sensed electric current (I
sEN) relevant.Particularly, enter I
sEN+the result electric current of pin and channel current I
lproportional.Then I
sENelectric current is sampled and keeps after abundant setting time, as well known in the field in this technique.Sample rate current can be used for comprising in the application of channel current balance, loaded line adjustment and overcurrent protection.
R in circuit 100 and 140
sENSEbeing provided in chip is outward because R
sENSEneed to be adjustable, thereby obtain the expectation I for circuit 100
oUTvalue is for DCR and I
iNDvarious combination.For example,, if I
oUTcompare to produce overcurrent release with the fixed current value that integrated circuit (IC) is inner, and inductor DCR and desired I
iNDcurrent-release point arranges by system restriction, R
sENSEvalue must be adjusted to expect I
iNDi is expected in upper acquisition
oUT.Because need the cause of adjustability, so R
sENSEconventionally be arranged on as shown in Figure 1 the outside of IC.R
sENSEconventionally second reason that is arranged on IC outside is that most of integrated circuit technologies are not supported accurate and stable internal resistor.
Use outside R
sENSEa problem be I
sENSE+the susceptibility of pin to the noise jamming as shown in Fig. 1 (a) and 1 (b), this noise jamming is the noise being coupled by capacitor parasitics 130.Refer again to Fig. 1 (a), be capacitively coupled to pin I
sENSE+noise current be revealed as the drain current of the Q1 that comprises noise component(s) shown in Fig. 1, be I
oUT+Noise.Known this noise coupling can have a negative impact to performance, and has required very meticulous printed circuit board wiring to minimize pin I
sENSE+on capacitive coupling.Conventionally attempt I
sENSE+it is infeasible being set as bypass, dispose into a limit, thereby may make A1 unstable because this understands in the feedback of amplifier A1.
Thereby, need to be through improved switching regulation circuit, particularly be used in the current measurement circuit of accurate sensing lead electric current in switching regulation circuit, circuit for controlling motor etc., they need to not have outside accurate R on the inverting input of A1 with additional noise susceptibility
sENSE.
Summary of the invention
DC-DC converter comprises: the chip that includes the pulse-width modulator (PWM) that error amplifier and input be connected to error amplifier output; By with the output node (V of this converter
oUT) inductor that the described PWM of series connection drives, wherein load current flows through inductor.V
oUTby comprising that the network-feedback of feedback resistance (RFB) is to the inverting input of error amplifier.Circuit for inductive load current comprises: the first operational amplifier; On chip, there is resistance R
sENSEthe inductive reactance of the inverting input that is coupled to the first amplifier; The induced current that is wherein relevant to load current flows through inductive reactance, and correlated current source provides output current with supply induced current.Reference resistance is arranged on chip and has the R of being
sENSEthe resistance R of fixing multiple
rEFERENCE.Set resistance and be arranged to there is resistance R
sET.Tracking circuit is arranged to equal to set ohmically voltage by the voltage on reference resistance.Functional block is coupled to receive electric current by setting resistance and obtain their ratio by the electric current of reference resistance.Electric current multiplier is configured to the wherein output of functional block and is connected to this electric current multiplier.Electric current multiplier provides with load current divided by R
sETproportional measurement electric current.
The present invention can utilize the various Circnit Layouts for inductive load current.In one embodiment, use inductor DCR induction, wherein converter also comprises the resistance of the capacitor's series of placing with leap inductor, and this resistance has the DC resistance (DCR) that is designed to the time constant matching with the time constant of inductor and be associated.In another embodiment, use MOSFET r
dS (ON)induction, wherein converter also comprises the synchronous rectifier between output and the inductor that is connected in PWM.
Inductive reactance and described reference resistance are preferably manufactured from the same material.In one embodiment, converter comprises current mirror, it has and is connected to the output of error amplifier end of oppisite phase and the input for measurement of inductance electric current, described current mirror becomes source electric current to flow through RFB described measurement current conversion, controls output impedance with the electromotive force that improves the inverting input of described error amplifier along with the increase of measurement electric current.In another embodiment, converter also comprises and makes comparisons and produce and apply a reset signal and enter the structure of overcurrent condition to PWM to prevent PWM measuring electric current and fixed reference electric current.In this embodiment, can comprise converter for structure relatively, the output of this converter is coupled to the replacement pin of converter, is greater than reference current if wherein measure electric current, and PWM will be forbidden.
In DC-DC converter, the method for electric current induction comprises the following steps: DC-DC converter chip is provided, it comprises is coupled to the error amplifier of pulse-width modulator (PWM) that drives inductor, this inductor be suitable for by the output node (V of the converter of load ground connection
oUT) series connection, wherein load current flows through described inductor.V
oUTreturn the inverting input of error amplifier via the network-feedback that comprises feedback resistance (RFB).Be used for the circuit that comprises inductive reactance of inductive load current at chip, this inductive reactance has for generation of the faradic resistance value (R that is relevant to load current
sENSE).Correlated current source provides output current (I
oUT) so that induced current to be provided.Reference resistance is arranged on chip and has the R of being
sENSEthe resistance R of fixing multiple
rEFERENCE.Be provided with and there is resistance R
sETsetting resistance, be also provided with the tracking circuit for the voltage on reference resistance being arranged to equal to set ohmically voltage.
The electric current of setting resistance of flowing through is determined with the ratio of electric current of the reference resistance of flowing through.Then with described R
sENSEthe irrelevant measurement electric current of actual value determine with this ratio, this measurement electric current and load current are divided by R
sETproportional.
Can realize inductor DCR induction for responding to the circuit of described load current.In another embodiment, realize MOSFET r for responding to the circuit of described load current
dS (ON)induction.
The method also can comprise utilizing measures electric current so that the step of fixing output impedance to be provided.In this embodiment, this utilizes step to comprise measurement electric current (normally Absorption Current) is transformed into source electric current, and the source electric current of making flows through feedback resistance to increase along with the increase of inductive current on inverting input with respect to V
oUTvoltage.
In another embodiment of the present invention, the method is further comprising the steps of: exceed scheduled volume if load current increases to, utilize measurement electric current to close PWM to avoid PWM to enter overcurrent condition.In this embodiment, this utilizes step to comprise: measurement electric current and predetermined reference current are made comparisons, be greater than reference current and if measure electric current, be cut to the power supply of described PWM.In one embodiment, measure electric current and reference current and be all configured to input inverter, the output of this inverter is coupled to the replacement pin of adjuster, is greater than reference current, PWM forbidding if wherein measure electric current.
Brief description of the drawings
By consulting following detail specifications and accompanying drawing, the present invention with and the complete understanding of feature and advantage can be accomplished, wherein
Fig. 1 (a) is the schematic diagram of realizing the known load electric current induction of inductor DCR induction in DC-DC converter.
Fig. 1 (b) is in the time that PWM drives synchronous rectifier, in DC-DC converter, realizes r
dS (ON)the schematic diagram of the known circuit of the load current induction of induction.
Fig. 2 illustrates the circuit of the induced inside resistance according to an embodiment of the invention with the inductive current for measuring DC-DC converter.
Fig. 3 illustrates and comprises with inductor DCR according to another embodiment of the present invention and respond to and come sensing lead electric current, schematic diagram with the exemplary DC-DC converter of the circuit of the output impedance of control change device.
Fig. 4 illustrates and comprises reusing according to the inductor DCR of further embodiment of this invention and respond to and come sensing lead electric current, schematic diagram with the exemplary DC-DC converter of the circuit of the PWM power supply of overcurrent release action protection converter.
Embodiment
Have according to an embodiment of the invention to realize in the DC-DC converter of inductor DCR induction or other switching regulation circuit circuit for the induced inside resistance of load current induction shown in Figure 2.Circuit 200 comprises and circuit element identical in circuit 100 shown in Fig. 1 (a), but added the adjunct circuit 250 (illustrating in dotted line) that comprises benchmark and tracking circuit, this benchmark and tracking circuit make the to flow through inductive current of inductor 110 can have nothing to do in R
sENSE120 actual value is measured.The same with circuit 100, circuit 200 comprises the part and common part (inductor L 110 and C in IC outside in IC inside conventionally
fILTERconventionally in IC outside).But, different from circuit 100 shown in Fig. 1, R
sENSEin IC inside.
Circuit 200 is included in I
oUTelectric current multiplier 215 on path is I to form
oUTmultiple, equal M*I
oUToutput current I
oUT2.Circuit 200 arranges the second resistance R in IC inside
rEFERENCE220.R
rEFERENCE220 owing to being placed in R on chip
sENSEnear 120 and by with R
sENSE120 identical electric conducting materials are made, so can be manufactured with accurate control and R
sENSEresistance ratio K., R
rEFERENCE=K*R
sENSE.K can be independent of process reform or temperature change obtains, and can be to be greater than or less than arbitrarily 1 convenient value.Circuit 200 also comprises non-essential resistance R
sET235.R
sETthe voltage of 235 high potential sides is shown to be coupled to V
cC, and R
sET235 low potential side is driven into any reference voltage.As shown in Figure 2, R
sETany reference voltage of 235 low potential sides arranges by the exemplary circuit that comprises voltage source V 1, and this voltage source V 1 is coupled to Pmos source follower Q2.
As in common knowledge in those skilled in the art, the source electrode of MOS transistor can exchange role at transistor duration of work with drain electrode.Therefore, serving as source electrode or drain in being not intended to respect to the special time at circuit working with " drain electrode " and limit the performed function of current-carrying electrode for identifying the term " source electrode " of current-carrying electrode of MOS transistor herein and in claim.
Operational amplifier A
2250 link together to drive R with Pmos Q3 255
rEFERENCE220 low potential end, thereby R
rEFERENCE220 have in fact and R
sET235 identical voltages.R
rEFERENCE220 can be by other drives such as NPN/PNP mixing follower, but in application-specific, system accuracy requires to get rid of the method.From R
rEFERENCE220 electric current with from R
sET235 electric current is fed to functional block F1 260.F1 can expand a multiplier multiple M by well-known analog or digital circuit, and this multiple M equals to pass through R
sETelectric current with pass through R
rEFERENCEthe ratio of electric current.Because electric current and each resistance value of the resistance by having same potential on it are inversely proportional to, so M equals R
rEFERENCE/ R
sET.Because R
rEFERENCEequal K*R
sENSEso, M=K*R
sENSE/ R
sET.
As mentioned above for circuit 100 shown in Fig. 1, output current I
oUTequal I
iND* DCR/R
sENSE.I
OUT2＝M*I
OUT＝M*I
IND*DCR/R
SENSE。Use K*R
sENSE/ R
sETsubstitute M:
I
OUT2＝K*DCR/R
SET (1)
Importantly, in equation (1), there is no R
sET, and I
oUT2only depend on external circuit elements (L and R
sET, and the DC resistance (DCR) of L) value.Therefore, do not require R
sENSEaccurate.R
sENSE120 relative R of needs
rEFERENCEhave fixed ratio (K), this fixed ratio is easy to arrange by circuit design.Because resistance is proportional, so for R
sENSEwith R
rEFERENCEthe resistivity of electric conducting material in the change of technique (or temperature) precision of the current measurement being provided by circuit 200 can be provided.
Pmos follower (Q2 and Q3) is illustrated as driving R
sENSE235 and R
rEFERENCE220, and R
sENSEwith R
rEFERENCEbe illustrated as termination positive supply VCC.Although what illustrate is Pmos follower, driver also may be selected to be the bipolar transistor of NMOS or arbitrary polarity, but and termination ground connection or other power supply.If be presented as nmos drive transistor, drive the suitably reverse of polarity and the termination of voltage reference V1 of Q2 grid.
Although not shown in Figure 2, R
rEFERENCE220 can drive by reference voltage V 1 and follower, and R
sETcan effectively be driven by A2 and Q3.This is normally lower than desired, because R
sETparasitic capacitance can in the feedback of A2250, produce a limit, this can cause A2 unstable.
Circuit 200 can be used for providing the switching regulation circuit that benefits from the inductive current of accurately measuring through improved, such as DC-DC converter, circuit for controlling motor etc.
Fig. 3 and Fig. 4 show induced current I
oUT2with respect to the exemplary use of the DC-DC converter of pulse width modulation.Fig. 3 has illustrated the output impedance of control change device, and Fig. 4 illustrates use overcurrent release action protection PWM power supply.But, noting, the present invention is not limited to the DC-DC converter of pulse width modulation, because it may be used on Other related equipment.In addition, as mentioned above, the load current sensor circuit that is different from the circuit based on inductor DCR induction can be applicable to the present invention.For example, shown in Fig. 1 (b), realize MOSFET r
dS (ON)the replaceable use of device of electric current induction, wherein induction connection (
with
) be connected to source electrode and the drain electrode thereof of lower FET (ground connection).Other suitable load current sensor circuit also can be used for the present invention.
Referring now to Fig. 3, the schematic diagram of exemplary PWM DC-DC converter 300 is shown, this converter 300 comprises: for measure the pin of crossing over inductor 110 according to the present invention
with
the circuit 310 of inductive current, this capacitor CF is formed for the low pass filter of load RL together with inductor 110.Converter 300 comprises error amplifier 350, and this error amplifier 350 is by applied reference voltage V
rEFwith through regulation output voltage V
oUTmake comparisons.V
oUTfeed back to the inverting input of amplifier 350 through resistance R FB, node FB.Other is coupling in compensating element, RC1 between output node COMP and the node FB of error amplifier 350 and CC1 is for suitable system responses is provided.Node COMP driving pulse width modulator PWM 360, this pulse-width modulator PWM 360 arranges some relations between its COMP voltage input and duty cycle output.Provide the conventional oscillator of clock signal (for example sawtooth waveforms) not to be illustrated to the input of PWM 360.PWM output signal PWM
oUTbecome output voltage V by inductor LF 110 with capacitor CF low-pass filter
oUT.It is that adjuster has appointment output impedance that the typical case of DC-DC converter requires.Be V
oUTmust be with respect to the load current I increasing
lOADreduce to fixing appointment output impedance is provided with fixed ratio.
Circuit 310 for inductance measuring electric current is used in the converter 300 shown in Fig. 3, to respond to by the electric current of LF 110, should be essentially identical electric current with the above-mentioned electric current by load RL on average by the electric current of LF 110.Can be presented as circuit 200 for the circuit 310 of measuring electric current, this circuit 200 comprises the R that crosses over LF 110
iNDwith C
iND, V on chip
oUTwith
r between pin
sENSE, and shown in the R shown in circuit 200
sETadd together pin to
with
other exemplary circuit on right side.
The electric current I being produced by the circuit 310 for inductance measuring electric current
oUT2be applied in, and used current mirror and there is suitable polarity.The output of current mirror 330 is to be expressed as I
oUT2source electric current, its RFB that flows through, thus along with I
lOADincrease and with respect to V
oUTincrease the voltage on node FB.Then error amplifier 350 reduces V
oUTvoltage, thereby node FB keeps equaling V
rEF, thereby desired fixing output impedance is provided.
Fig. 4 shows for according to the second exemplary application of inductive current induction circuit of the present invention.Fig. 4 shows the schematic diagram of exemplary PWM DC-DC converter 400, and this PWM DC-DC converter 400 comprises in a circuit according to the invention 310, and this circuit 310, for inductance measuring electric current, is used for overcurrent release action protection PWM power supply.As described in respect to Fig. 3, can be presented as the exemplary measuring circuit shown in Fig. 2 for measuring the circuit 310 of electric current.
In the time of work, if load current I
lOADincrease to and exceed scheduled current level, can cut off the power supply of PWM 360 according to the circuit 310 for inductance measuring electric current of the present invention.In one embodiment, inverter 435 is coupled to the replacement pin of PWM 360.I
oUT2with provided fixed reference electric current I
rEFmake comparisons.Requiring replacement pin for normal running is for high converter, if I
oUT2be greater than I
rEF, the input of inverter 435 will be dragged down, and this will cause inverter to uprise and send reset signal making PWM 360 disabled to PWM 360, thereby prevent that PWM360 from entering overcurrent condition.
This invention provides some remarkable advantages.An advantage is exactly R
sENSEon chip, be an inner node thereby cause the anti-phase input of A1, and therefore shield the capacitive coupling of noise.In circuit 200
with
node is all low-impedance, so be more not easy to be subject to noise jamming.Another advantage is exactly from non-essential resistance R
sETinput can be DC or low frequency because it can not affect from I
sENSEto I
oUT2the bandwidth in path.Therefore R
sETcan be set as bypass (by-pass capacitor is not shown) to prevent noise jamming.
Also having an advantage is exactly R
sETcan be used to control I
sENSEto I
oUT2some passages.This with each passage is used to separate outer R
sETcompare and can save element.Another advantage is exactly that thermistor can be used to temperature change R
sETvalue, and by I
oUT2gain adjust to the conductive coefficient of inductor DCR and match.Positive temperature coefficient thermistor (PTC) or PTC-resistor network can be used to replace R
sET.PTC or PTC-resistor network may be selected to be has the temperature coefficient identical with the DCR of inductor, and will be placed be convenient to heat follow the tracks of inductor.Along with the increase of inductor temperature and the therefore increase of its DCR value, the constant ratio of given induced current and actual inductive current, the similar resistance value of PTC or PTC-resistor network increases and will reduce the gain amplifier of sensor circuit.Thermistor is set as bypass to prevent noise jamming near IC.
Be understandable that, described the present invention although combine preferred specific embodiment of the present invention, description above and example below are all intended to explanation but not limit the scope of the invention.Other side, advantage and change in the scope of the invention are apparent for those skilled in the art of the invention.
Claims (19)
1. a power inverter, described power inverter comprises:
Set resistance, its resistance value is R
set, described setting resistance is used to control some passages;
Error amplifier, is configured to reference voltage and makes comparisons through regulation output voltage;
Pulse-width modulator, is coupled to described error amplifier and is configured to based on the described output voltage through regulating of relatively changing in described error amplifier; And
Current sensing elements, is coupled to described pulse-width modulator and is configured to respond to the first electric current;
Inductive reactance, its resistance value is R
sense, described inductive reactance is coupled to described current sensing elements so that the first electric current sensing flows through described inductive reactance;
Reference resistance, has the R of being
sensethe resistance value R of fixing multiple
reference; And
The circuit that is coupled to described setting resistance, described reference resistance and described inductive reactance, described circuit is configured to produce output current, the same R of value of described output current
setand one fixed ratio proportional, wherein said fixed ratio is R
sensewith R
referenceratio, wherein said which couple to described error amplifier to provide described output current to described error amplifier.
2. power inverter as claimed in claim 1, is characterized in that, described current sensing elements is realized inductor D.C. resistance (DCR) induction.
3. power inverter as claimed in claim 1, is characterized in that, described circuit comprises tracking circuit, and described tracking circuit is configured to drive described reference resistance so that the voltage on described reference resistance equals the ohmically voltage of described setting.
4. power inverter as claimed in claim 1, is characterized in that, described circuit is configured to definite R that passes through
setelectric current with pass through R
referencethe ratio of electric current, and R is passed through in combination
setelectric current with pass through R
referenceelectric current ratio and first measure electric current to produce described output current.
5. power inverter as claimed in claim 3, is characterized in that, described tracking circuit comprises:
Source follower, is coupled to the low potential end of described reference resistance; And
Operational amplifier, has the output of the grid that is coupled to described source follower.
6. power inverter as claimed in claim 1, is characterized in that, described setting resistance comprises multiple resistance that comprises one or more thermistors.
7. power inverter as claimed in claim 1, is characterized in that, described reference resistance and described inductive reactance are made up of the material of same type.
8. power inverter as claimed in claim 1, it is characterized in that, also comprise the inverter of the replacement pin that is coupled to described pulse-width modulator, if wherein described output current is greater than reference current, described inverter sends reset signal to described pulse-width modulator.
9. power inverter as claimed in claim 1, it is characterized in that, also comprise the current mirror being coupling between the output of integrated circuit and the input of described error amplifier, wherein said current mirror increases the voltage of input of described error amplifier so that described power inverter provides fixing output impedance based on described output current.
10. for measuring the equipment of load current of each channel for multiple channels, described equipment comprises:
Set resistance, its resistance value is R
set; And
Be coupled to the integrated circuit of described setting resistance; Wherein, for each channel of described multiple channels, described integrated circuit comprises:
Inductive reactance, its resistance value is R
sense, described inductive reactance is coupled to corresponding current sensing elements so that flow through described inductive reactance from corresponding first induced current of described current sensing elements;
Reference resistance, has the R of being
sensethe resistance value R of fixing multiple
reference; And
The circuit that is coupled to described setting resistance, described reference resistance and described inductive reactance, described circuit is configured to produce output current, the same R of value of described output current
setand one fixed ratio proportional, wherein said fixed ratio is R
sensewith R
referenceratio.
11. equipment as claimed in claim 10, is characterized in that, for each channel of described multiple channels, described inductive reactance is coupled to the current sensing elements of realizing inductor D.C. resistance (DCR) induction.
12. equipment as claimed in claim 10, it is characterized in that, for each channel of described multiple channels, described circuit in described integrated circuit comprises tracking circuit, and described tracking circuit is configured to drive described reference resistance so that the voltage on described reference resistance equals the ohmically voltage of described setting.
13. equipment as claimed in claim 12, is characterized in that, described tracking circuit comprises:
Source follower, is coupled to the low potential end of described reference resistance; And
Operational amplifier, has the output of the grid that is coupled to described source follower.
14. equipment as claimed in claim 12, is characterized in that, for each channel of described multiple channels, the circuit in described integrated circuit is configured to definite R that passes through
setelectric current with pass through R
referencethe ratio of electric current, and R is passed through in combination
setelectric current with pass through R
referenceelectric current ratio and first measure electric current to produce described output current.
15. equipment as claimed in claim 10, is characterized in that, described setting resistance comprises multiple resistance that comprises one or more thermistors.
16. equipment as claimed in claim 10, is characterized in that, described reference resistance and described inductive reactance are made up of the material of same type.
17. equipment as claimed in claim 10, is characterized in that, for each channel of described multiple channels, described inductive reactance is coupled to the current sensing elements of realizing MOSFETRDS (on) induction.
18. 1 kinds for measuring the method for load current of each channel of multiple channels, and described method is included as each channel of described multiple channels:
Receive corresponding induced current;
By the induced current of receiving by thering is accordingly the first resistance of the first resistance value;
Generate instruction based on described the first resistance value and measure electric current from corresponding first of described corresponding faradic load current;
Set corresponding the second ohmically voltage and equal the 3rd ohmically voltage, described the 3rd resistance has the 3rd resistance value, and each channel of wherein said multiple channels uses the 3rd identical resistance;
Determine the ratio that flows through the electric current of described corresponding the second resistance and flow through the electric current of described the 3rd resistance, wherein each corresponding the second resistance has the second resistance value for the fixing multiple of described corresponding the first resistance;
Combine described corresponding the first measurement electric current and determined ratio and measure electric current to generate corresponding second of the described load current of instruction, described corresponding second measures electric current is independent of described corresponding the first resistance value; And
Export described corresponding second and measure electric current.
19. methods as claimed in claim 18, is characterized in that, also comprise that described corresponding the second resistance value of amendment is to regulate described the corresponding second gain of measuring electric current.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US80819706P | 2006-05-24 | 2006-05-24 | |
| US60/808,197 | 2006-05-24 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2006101365840A Division CN101079575B (en) | 2006-05-24 | 2006-10-23 | DC-DC converters having improved current sensing and related methods |
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| Publication Number | Publication Date |
|---|---|
| CN102299627A CN102299627A (en) | 2011-12-28 |
| CN102299627B true CN102299627B (en) | 2014-11-12 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2006101365840A Expired - Fee Related CN101079575B (en) | 2006-05-24 | 2006-10-23 | DC-DC converters having improved current sensing and related methods |
| CN201110128753.7A Expired - Fee Related CN102299627B (en) | 2006-05-24 | 2006-10-23 | DC-DC converters having improved current sensing and related methods |
| CN201410240027.8A Pending CN103986328A (en) | 2006-05-24 | 2006-10-23 | DC-DC converters having improved current sensing and related methods |
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| CN2006101365840A Expired - Fee Related CN101079575B (en) | 2006-05-24 | 2006-10-23 | DC-DC converters having improved current sensing and related methods |
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| Application Number | Title | Priority Date | Filing Date |
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| CN201410240027.8A Pending CN103986328A (en) | 2006-05-24 | 2006-10-23 | DC-DC converters having improved current sensing and related methods |
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| CN (3) | CN101079575B (en) |
| TW (1) | TWI404316B (en) |
Families Citing this family (14)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7816978B1 (en) * | 2009-07-20 | 2010-10-19 | Mediatek Inc. | Operating circuit with RC calibration and RC calibration method |
| US8779777B2 (en) | 2010-06-04 | 2014-07-15 | Linear Technology Corporation | Dynamic compensation of aging drift in current sense resistor |
| TWI473000B (en) * | 2012-03-12 | 2015-02-11 | Egalax Empia Technology Inc | Signal sensing circuit |
| CN103294091B (en) * | 2013-06-28 | 2014-10-15 | 电子科技大学 | Voltage type feedback circuit suitable for DC-DC (Direct Current) converter |
| CN104467406A (en) * | 2013-09-13 | 2015-03-25 | 杭州必易科技有限公司 | Led constant current driver |
| US9748843B2 (en) * | 2014-09-24 | 2017-08-29 | Linear Technology Corporation | DCR inductor current-sensing in four-switch buck-boost converters |
| TWI585421B (en) | 2015-05-22 | 2017-06-01 | 登騰電子股份有限公司 | Current sensing module and power conversion apparatus and electronic apparatus using the same |
| US10024889B2 (en) * | 2015-12-23 | 2018-07-17 | Intel IP Corporation | Apparatuses, methods, and systems for detection of a current level |
| CN108258900B (en) * | 2016-12-28 | 2019-12-27 | 上海甄平半导体有限公司 | DC-DC converter and power modulator |
| CN106771502A (en) * | 2017-02-06 | 2017-05-31 | 山东鲁能智能技术有限公司 | A kind of circuit and method for improving source current overload protection ability |
| CN109921639B (en) * | 2019-03-18 | 2021-02-12 | 电子科技大学 | Buck converter based on variable conduction time control |
| US10666197B1 (en) * | 2019-06-03 | 2020-05-26 | Realtek Semiconductor Corp. | Low noise crystal oscillator and method thereof |
| US11175319B1 (en) * | 2020-09-18 | 2021-11-16 | Stmicroelectronics Asia Pacific Pte Ltd | High accuracy low temperature drift high-side current sensing hardware and method |
| TWI774491B (en) * | 2021-07-28 | 2022-08-11 | 瑞昱半導體股份有限公司 | Voltage regulator device |
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| CN1165560A (en) * | 1995-09-14 | 1997-11-19 | Abb研究有限公司 | Device for sensing of electric discharges in a test object |
| GB2320762A (en) * | 1996-11-08 | 1998-07-01 | Int Rectifier Corp | Circuit for sensing motor load current |
| US6040689A (en) * | 1997-06-17 | 2000-03-21 | Ssac, Inc. | Current sensing method and apparatus |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| US5982160A (en) * | 1998-12-24 | 1999-11-09 | Harris Corporation | DC-to-DC converter with inductor current sensing and related methods |
| TWI220022B (en) * | 2002-05-27 | 2004-08-01 | Richtek Technology Corp | Current sensing apparatus and method |
| TW576007B (en) * | 2002-09-20 | 2004-02-11 | Richtek Technology Corp | Semi-simulating current sensing apparatus and method for switching mode DC/DC power source converter |
| US7394630B2 (en) * | 2002-10-11 | 2008-07-01 | Ming-Dou Ker | Electrostatic discharge protection device for mixed voltage interface |
| CN1717857A (en) * | 2002-11-29 | 2006-01-04 | 索尼株式会社 | Switching power supply circuit |
| TWI235541B (en) * | 2004-06-25 | 2005-07-01 | Anpec Electronics Corp | Current detection circuit and method for use in DC-to-DC converter |
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2006
- 2006-10-04 TW TW95136835A patent/TWI404316B/en not_active IP Right Cessation
- 2006-10-23 CN CN2006101365840A patent/CN101079575B/en not_active Expired - Fee Related
- 2006-10-23 CN CN201110128753.7A patent/CN102299627B/en not_active Expired - Fee Related
- 2006-10-23 CN CN201410240027.8A patent/CN103986328A/en active Pending
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1165560A (en) * | 1995-09-14 | 1997-11-19 | Abb研究有限公司 | Device for sensing of electric discharges in a test object |
| GB2320762A (en) * | 1996-11-08 | 1998-07-01 | Int Rectifier Corp | Circuit for sensing motor load current |
| US6040689A (en) * | 1997-06-17 | 2000-03-21 | Ssac, Inc. | Current sensing method and apparatus |
Also Published As
| Publication number | Publication date |
|---|---|
| CN103986328A (en) | 2014-08-13 |
| CN101079575A (en) | 2007-11-28 |
| TW200744293A (en) | 2007-12-01 |
| CN102299627A (en) | 2011-12-28 |
| TWI404316B (en) | 2013-08-01 |
| CN101079575B (en) | 2012-08-29 |
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