CN103888155B - Radio frequency sending set, integrated circuit (IC)-components, wireless communication unit and correlation technique - Google Patents
Radio frequency sending set, integrated circuit (IC)-components, wireless communication unit and correlation technique Download PDFInfo
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- CN103888155B CN103888155B CN201310687199.5A CN201310687199A CN103888155B CN 103888155 B CN103888155 B CN 103888155B CN 201310687199 A CN201310687199 A CN 201310687199A CN 103888155 B CN103888155 B CN 103888155B
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Abstract
The embodiment of the present invention provides a kind of radio frequency sending set, integrated circuit (IC)-components, wireless communication unit and correlation technique, and wherein RF transmitter comprises: the power amplifier comprising multiple Power Amplifier Unit; Be coupled at least one signal processing module of power amplifier, comprise at least one digital pre-distortion assembly, for apply via a digital filter at least one digital pre-distortion code word to multiple Power Amplifier Unit at least one in; And combiner, combine to produce an analog rf signal to multiple outputs of multiple Power Amplifier Unit based at least one digital pre-distortion code word after digital filtering at least part of, this analog rf signal is used for being transmitted by a RF interface.The embodiment of the present invention can slow down the impact of DAC image in digital RF transmitter, and arrowband and wide-band modulation input signal can be applicable to simultaneously, compared to traditional RF transmitter architecture, the embodiment of the present invention more can benefit from measurability that numeric field has and high efficiency advantage.
Description
[technical field]
The invention relates to a kind of radio frequency (RF) transmitter, integrated circuit (IC)-components, wireless communication unit and correlation technique, the present invention is applied to but does not limit and is applied to the method for radiofrequency signal of a kind of generation for transmitting at radio frequency interface place.
[background technology]
Deep sub-micron Complimentary metal-oxide semiconductor (MOS) (ComplementaryMetal-Oxide-SemiconductorTransistor, COMS) development of process makes the size of digital circuit become more and more less and has more and more higher power-efficient, but can not have influence on the change of the size of analog circuit especially.Therefore for some device, such as RF transmitter, needs under the help of such as digital signal processing algorithm, reduces the analog element in device or circuit as much as possible, to make deep-submicron CMOS process better to be carried out, and then therefrom benefits.
In addition, the RF transmitter traditional due to major part all can use linear power amplifier (PA), and based on the inefficient characteristic of this linear PA, the power efficiency of traditional RF transmitter of the type also usually can be very low.By contrast, the PA of switching mode has higher power efficiency, thus also makes RF transmitter be more prone to use this kind of PA to substitute traditional linear PA.Therefore, a kind of switching mode PA that can use under the help of digital processing algorithm is needed badly to reduce the size of PA and to improve the RF transmitter of the power efficiency of PA.But the PA of switching mode has nonlinear Input output Relationship usually, in addition, in order to meet the active demand that current each wireless standard coexists, usually also need to be applied to noise shaping techniques.
Digital Polarity transmitter is a kind of known transmitter design using switching mode PA, utilize CMOS technology technology simultaneously.Therefore, this kind of Digital Polarity transmitter can realize high power efficiency, only needs very little silicon area simultaneously.But the defect of this Digital Polarity transmitter is: because in a polar structure, Modulation and Amplitude Modulation (AM) signal and phase-modulation (PM) signal have intrinsic bandwidth extended attribute, therefore this Digital Polarity transmitter is only applicable to narrow bandwidth modulation signal.
Mixing polar transmitter utilizes two-dimensional modulation (inphase/orthogonal phase) technology to realize wideband phase modulation.But the defect of this mixing polar transmitter is, it needs to bear amplitude quantization noise and phase quantisation noise two kinds of noises simultaneously, therefore mixes polar transmitter and more needs using noise shaping technique.
Transmitter based on inphase/orthogonal phase (I/Q) RF digital to analog converter (DAC) is similarly a kind of known transmitter design.I/QRFDAC combines the function of DAC and frequency mixer, and the output of this I/QRFDAC is merged in simulation (RF) territory simultaneously.But this transmitter design needs a linear PA, and the power efficiency of direct I/QRF analog conversion function is lower than the power efficiency of Digital Polarity transmitter.
Another kind of known (being mainly arrowband) RF transmitter design uses suitable pre-distortion technology, and this pre-distortion technology utilizes non-linear with auto-reverse power amplifier of delta sigma modulator.This transmitter design is relatively simple and allow the use of low accuracy DAC, but this transmitter design still comprises traditional framework, and therefore the power efficiency of PA is still very low.
The RF transmitter of pre-interim another kind digital auxiliary type/digital Dense type fast development will become demand, but, because digital algorithm is limited to the feasibility of circuit speed, therefore from enforcement angle, seeking a kind of simple and effective digital algorithm is the key realizing this kind of transmitter.
First refer to Fig. 1, Figure 1 shows that a kind of simple structure schematic diagram of digital to RF converter 100, this digital to RF converter 100 is for performing modulation operations to RF signal.This digital to RF converter 100 is for receiving a RF signal, the digital word signal (digital control word) 120 received according to one in digital-to-RF transmitter 140 is modulated the RF signal received, and exporting the rear RF signal 130 of a modulation accordingly, the RF signal of wherein this reception is such as comprising the RF signal 110 of constant envelope.The analog baseband signal be usually found in traditional transmitter is not comprised in this digital-to-RF transmitter 140.And, digital word signal 120 and RF signal direct conversion.This output waveform is RF signal 130 after a modulation.
Figure 2 shows that existing a kind of use is applied to the simple structure schematic diagram of the RF transmitter of the digital pre-distortion code word of digital power amplifier.Module 205 produces digital pre-distortion (DPD) code word and is inputed to the first digital power amplifier circuit (DPA1) 210.This DPD code word is also input to the second digital power amplifier circuit (DPA2) 220, to produce the orthogonal signalling of this DPD code word 205 by Postponement module 215 simultaneously.The output of the first digital power amplifier circuit (DPA1) 210 and the output of the second digital power amplifier circuit (DPA2) 220 are provided to an addition module 230, using produce add the General Logistics Department RF power amplified signal as output 235.
For each RF transmitter, it all relates to the problem that the digital word for the analog module in control figure RF transmitter only can change with a certain characteristic frequency.Therefore, based on digital sample operation, the RF output spectrum of often kind of RF transmitter is all rendered as the repetition of peri odic spectrum, they can be referred to as digital-to-analogue conversion (DAC) image, such as, signal waveform 300,305,310,315 shown in Fig. 3.Figure 3 shows that the schematic diagram of the DAC image in digital RF transmitter.This will cause so-called DAC image 320 to be sampled frequency in RF output spectrum separating.This DAC image cannot meet the demand coexisted in power spectral density demand or equipment.In traditional RF transmitter, after simulation low-pass filter is usually arranged on and follows DAC closely, for the generation slowing down this DAC image.But, in digital RF transmitter, it does not possess this Analog Baseband filter capacity, and the impact (such as by RF filter slow down effect) therefore how slowing down this DAC image in digital RF transmitter becomes the important problem of of needing to solve with the violation eliminating or minimize any PSD under a rational cost price.
Therefore, the RF transmitter needing a kind of improvement badly with and related methods to solve the problem.
[summary of the invention]
In view of this, the embodiment of the present invention is intended to provide a kind of radio frequency sending set, integrated circuit (IC)-components, wireless communication unit and correlation technique, to produce the RF signal for being transmitted by RF interface, to slow down, to eliminate above-mentioned one or more problem.
According to the first embodiment of the present invention, a kind of radio frequency RF transmitter is provided, comprises: the power amplifier comprising multiple Power Amplifier Unit; At least one signal processing module, be coupled to this power amplifier, this at least one signal processing module comprises at least one digital pre-distortion assembly, for applying at least one digital pre-distortion code word to multiple Power Amplifier Unit, wherein this at least one digital pre-distortion code word is applied at least one of the plurality of Power Amplifier Unit via a digital filter; And combiner, combine to produce an analog rf signal to multiple outputs of the plurality of Power Amplifier Unit based at least one digital pre-distortion code word after digital filtering at least part of, this analog rf signal is used for being transmitted by a RF interface.
According to a second embodiment of the present invention, a kind of integrated circuit (IC)-components is provided, comprise: at least one digital signal processing module, be coupled to a power amplifier, this power amplifier comprises multiple Power Amplifier Unit, wherein this at least one digital signal processing module comprises: at least one digital pre-distortion assembly, for applying at least one digital pre-distortion code word to the plurality of Power Amplifier Unit, wherein this at least one digital pre-distortion code word is applied at least one of the plurality of Power Amplifier Unit via a digital filter; And combiner, combine to produce an analog rf signal to multiple outputs of the plurality of Power Amplifier Unit based at least one digital pre-distortion code word after digital filtering at least part of, this analog rf signal is used for being transmitted by a RF interface.
According to the third embodiment of the invention, provide a kind of method of the RF signal for generation of being transmitted by RF interface, the method comprises: produce at least one digital pre-distortion code word; Apply in multiple Power Amplifier Unit of this at least one digital pre-distortion code word to power amplifier, wherein this at least one digital pre-distortion code word is applied at least one of the plurality of Power Amplifier Unit via a digital filter; And at least partly based at least one digital pre-distortion code word after digital filtering, combine to produce this RF signal to multiple outputs of the plurality of Power Amplifier Unit.
According to a fourth embodiment of the invention, a kind of RF transmitter is provided, comprises: the power amplifier comprising multiple Power Amplifier Unit; At least one signal processing module, is coupled to this power amplifier, and this at least one signal processing module comprises at least one digital pre-distortion assembly, and this at least one digital pre-distortion assembly is used for: implement interpolation operation to this at least one digital pre-distortion code word; And the interpolation part exporting this at least one digital pre-distortion code word is in a part at least one this Power Amplifier Unit of this power amplifier, and producing an analog rf signal based on this interpolation part of this at least one digital pre-distortion code word at least partly, this analog rf signal is used for being transmitted by a RF interface.
According to a fifth embodiment of the invention, a kind of integrated circuit (IC)-components is provided, comprise: at least one signal processing module, be coupled to a power amplifier, this power amplifier comprises multiple Power Amplifier Unit, wherein this at least one signal processing module comprises: at least one digital pre-distortion assembly, for implementing interpolation operation to this at least one digital pre-distortion code word; And the interpolation part exporting this at least one digital pre-distortion code word is in a part at least one this Power Amplifier Unit of this power amplifier, and producing an analog rf signal based on this interpolation part of this at least one digital pre-distortion code word at least partly, this analog rf signal is used for being transmitted by a RF interface.
According to a sixth embodiment of the invention, provide a kind of method of the RF signal for generation of being transmitted by RF interface, the method comprises: produce at least one digital pre-distortion code word; Apply in multiple Power Amplifier Unit of this at least one digital pre-distortion code word to power amplifier, this step comprises further: implement interpolation operation to this at least one digital pre-distortion code word; And the interpolation part exporting this at least one digital pre-distortion code word is in a part at least one this Power Amplifier Unit of this power amplifier, and producing an analog rf signal based on this interpolation part of this at least one digital pre-distortion code word at least partly, this analog rf signal is used for being transmitted by a RF interface.
The radio frequency sending set of the embodiment of the present invention, integrated circuit (IC)-components, wireless communication unit and correlation technique, the impact of DAC image can be slowed down in digital RF transmitter, and arrowband and wide-band modulation input signal can be applicable to simultaneously, compared to traditional RF transmitter architecture, the embodiment of the present invention more can benefit from measurability that numeric field has and high efficiency advantage.
[accompanying drawing explanation]
Figure 1 shows that a kind of simple structure schematic diagram of digital to RF converter;
Figure 2 shows that existing a kind of use is applied to the simple structure schematic diagram of the RF transmitter of the digital pre-distortion code word of digital power amplifier;
Figure 3 shows that the schematic diagram of the DAC image in digital RF transmitter;
Figure 4 shows that the part simple structure schematic diagram of the wireless communication unit according to one embodiment of the invention;
Figure 5 shows that the simple structure schematic diagram of the RF transmitter according to one embodiment of the invention;
Figure 6 shows that the simple structure schematic diagram of the RF transmitter according to another embodiment of the present invention;
Figure 7 shows that the simple structure schematic diagram of the RF transmitter according to further embodiment of this invention;
Figure 8 shows that the simple structure schematic diagram of an embodiment of the power amplifier module of Fig. 5;
Figure 9 shows that the simple structure schematic diagram of the RF transmitter according to yet another embodiment of the invention;
Figure 10 shows that, according to the embodiment of the present invention, full interpolation or part interpolation are implemented to be applied to the comparison schematic diagram of two kinds of execution modes of DPA to DPD code word;
Figure 11 shows that the simple structure schematic diagram of the RF transmitter going back an embodiment according to the present invention;
Figure 12 shows that the simple structure schematic diagram of the RF transmitter according to further embodiment of this invention;
Figure 13 shows that the use mixing multiphase filtering method of the foundation embodiment of the present invention is to reduce the simplified flow chart of DAC image;
Figure 14 shows that the use part interpolation method of the foundation embodiment of the present invention is to reduce the simplified flow chart of DAC image;
Figure 15 shows that according to using mixing multiphase filtering method and part interpolation method to reduce the simplified flow chart of DAC image while the embodiment of the present invention;
Figure 16 to 19 is depicted as the simple structure schematic diagram of the various digital-to-RF transmitters that can benefit from the embodiment of the present invention.
[embodiment]
Some vocabulary is employed to censure specific element in the middle of specification and follow-up claim.Those skilled in the art should understand, and same element may be called with different nouns by manufacturer.This specification and follow-up claim are not used as the mode of distinguish one element from another with the difference of title, but are used as the criterion of differentiation with element difference functionally." comprising " mentioned in the middle of specification and follow-up claim is in the whole text an open term, therefore should be construed to " comprise but be not limited to ".In addition, " couple " word should be interpreted as in this article comprising directly any and being indirectly electrically connected means.Therefore, if describe first device in literary composition to be coupled to the second device, then represent this first device and directly can be electrically connected in this second device, or be indirectly electrically connected to this second device by other devices or connection means.
The embodiment of the present invention is described for the RF transmitter be used in an aerogram mobile phone.But, those skilled in the art it is to be appreciated that, inventive concept described herein is not limited in the particular characteristics of cited embodiment, and it can also be applied and be implemented in other alternative communication units, transmitter, integrated circuit and application, and produces same effect.
First refer to Fig. 4, Figure 4 shows that the part simple structure schematic diagram of the wireless communication unit 400 according to one embodiment of the invention.In embodiments of the present invention, this wireless communication unit 400 can be an aerogram mobile phone.As shown in the figure, this wireless communication unit 400 comprises antenna 402 and is coupled to the multiple known radio frequency transceiver element/circuit of this antenna 402.In the present embodiment, this antenna 402 is coupled to one combining filter/duplexer 404, and this combining filter/duplexer 404 is in order to the isolation providing receive chain 406 and launch between chain 407.As understood by those skilled in the art, this receive chain 406 comprises radio-frequency transmitter circuit usually, to provide reception, filtering and intermediate frequency or fundamental frequency frequency down-conversion function.On the contrary, this transmitting chain 407 comprises radio frequency sending set circuit usually, modulates, amplifies and filter function to provide up-conversion.Up-converter circuit and lower frequency changer circuit receive the RF local oscillated signal from frequency generating circuit 430.
Further, this wireless communication unit 400 also comprises signal processing logic 408.One output of this signal processing logic 408 is provided to a suitable user interface (UI) 410, and this user interface 230 comprises such as a screen, keyboard, microphone or loud speaker etc.This signal processing logic 408 is also coupled to memory component 416, memory component 416 is for storing various operating mechanism, such as coding/decoding function and similar functions, and this memory component 416 realizes by various technology, such as random-access memory (ram), read-only memory (ROM), the combination in any of flash memory or these memory technologies and other memory technologies.In addition, a timer 418 can be coupled to this signal processing logic 408 usually, in order to control the sequential of various operation in wireless communication unit 400.
As understood by those skilled in the art, transmitting chain 407 in aerogram mobile phone comprises the transmitter circuitry for receiving input signal, in the present embodiment, this input signal can be such as the signal from signal processing logic 408, and this input signal comprises the information being about to be transmitted by a RF interface.This transmitting chain 407, also for exporting a RF signal, such as comprises the information being about to be sent to antenna 402 by duplexer 404 in this RF signal.For example, this transmitting chain 407 needs to perform the digital-to-analogue conversion of input signal, mixing, noise shaping and amplifieroperation to produce the output of RF signal.In certain embodiments, the digital signal processor of this transmitting chain 407 uses a digital pre-distortion code word to be applied in a digital power amplifier, is described in more detail with reference to subsequent drawings about this part content.
Refer to Fig. 5 now, Figure 5 shows that the simple structure schematic diagram of the RF transmitter 500 according to one embodiment of the invention, this RF transmitter 500 such as can be implemented in the transmitting chain 407 shown in Fig. 4 and signal processing logic 408.As shown in Figure 5, this RF transmitter 500 comprises a digital signal processing module 510, for receiving one or more input complex signal by the antenna 402 such as shown in Fig. 4, comprises the information being about to be transmitted by RF interface in this input complex signal.In the present embodiment, this digital signal processing module 510 is for from the signal processing logic 408 of digital baseband (DBB) element 521(such as shown in Fig. 4) receive IQ(inphase/orthogonal phase) input signal, this IQ input signal comprises the first signal (homophase) composition 522 and secondary signal (orthorhombic phase) composition 524.The IQ input signal 522 of this digital signal processing module 510 also for receiving, 524 are converted to (such as performing map operation) first in-phase digital code word 512 and second orthorhombic phase digital word 514, and exporting this first in-phase digital code word 512 and the second orthorhombic phase digital word 514 to power amplifier module (2D-DPA) 530 by IQ-PDAC module 540, it is a power DAC (PDAC) that this power amplifier module 530 can operate.
This power amplifier module 530 can comprise first (homophase) array and second (orthorhombic phase) array with multiple switch-mode-power unit.This power amplifier module 530 exports for receiving digital word, and at least partly based on the homophase received and orthorhombic phase digital word to produce an analog rf signal 532 for by the transmission of RF interface, such as transmitted by band pass filter 534 and antenna 402.
Therefore, this digital signal processing module 510 is digital word 512 for conversion (such as performing mapping function) this input signal 522,524,514.This digital word 512,514 comprises the high power analog conversion function to RF signal in PA module 530() with RF signal direct conversion to produce an output waveform, i.e. RF modulation signal.
In this fashion, RF transmitter 500 comprises one based on the structure of complex signal, such as, based on the structure of I/Q signal, thus to be applicable to arrowband and wide-band modulation input signal simultaneously.In contrast to such as Digital Polarity structure, this Digital Polarity structure only can be applicable to narrow-band modulated due to the intrinsic bandwidth extended attribute of AM input signal and PM input signal.In addition, the above-mentioned structure based on IQ also avoid the demand to complicated algorithm, such as, just usually needs in Digital Polarity structure to perform cordic algorithm.In addition, its numeric field can also be extended to power amplifier module 530 by this RF transmitter 500, thus compared to traditional RF structure, and this RF transmitter 500 more can benefit from measurability that numeric field has and high efficiency advantage.
Although in the integrated circuit that described in the embodiments a kind of discrete type shown in Fig. 5, this circuit at least comprises the above-mentioned signal processing module 510 being coupled to power amplifier module 530, but those skilled in the art can predict other integrated circuit form on this basis, wherein at least can comprise the function of signal processing module 510 and power amplifier module 530 simultaneously.
Refer to Fig. 6 now, Figure 6 shows that the simple structure schematic diagram of the RF transmitter 600 according to another embodiment of the present invention, this RF transmitter 600 can use digital pre-distortion code word 605 to be applied in mixing multiphase filter 625 and digital power amplifier, and this RF transmitter such as can operate in the digital signal processing module 408 shown in Fig. 4.In another embodiment, this mixing multiphase filter (h (n)) 625 can also be used another filter of the simple scalar gain factor or multiple filter factor replace.In embodiments of the present invention, this digital pre-distortion code word 605 can use multiple (IQ) signal of the input received from digital baseband element (not shown) by a signal processor, and performs conversion operations (such as performing map operation) to multiple (IQ) signal of this input received and produce.This digital pre-distortion code word 605 directly can apply (610) in the first digital power amplifier (DPA1) 615, this first digital power amplifier 615 can be such as a part for the PA module 530 shown in Fig. 5, comprises the high power analog conversion function to RF signal.This digital pre-distortion code word 605 can also be applied in the second digital power amplifier (DPA2) 635, to produce phase deviation in this signal path with delay element 630 via mixing multiphase filter 625.In certain embodiments, this phase deviation equals T/2, wherein T=1/fs, and fs is the sample frequency of codeword sequence x (n).In some embodiments of the invention, this mixing multiphase filter 625 can also be arranged in the path not comprising delay element 630; Or, in other embodiments, at two paths, all delay element can be set, such as, all produce the delay skew of T/2.In embodiments of the present invention, this mixing multiphase filter 625 combine digital filtering operation under sample frequency fs.And in other embodiments of the invention, the mode that can also be applicable to by other produces the phase deviation introduced by delay element 630, such as, by an interchangeable hardware element, or passes through the mode of software or firmware.Thus in this fashion, the digital clock frequencies of digital word can not be increased.
First digital power amplifier 615 and being output in combiner 620 of the second digital power amplifier 635 are combined and are produced output 640 to an antenna (not shown).It should be noted that because this RF transmitter 600 is a digital RF transmitter, therefore wherein do not comprise Analog Baseband filtering.
Under aforesaid way, based on the embodiment shown in Fig. 6, this RF transmitter can provide the linear interpolation DPA of one 2 times, and the last digital filter wherein entering to analog domain in digital signal is applied in the out of phase being different from (directly) DPA, thus.In this fashion, by careful control/select this mixing multiphase filter 625 and delay element 630, the power DAC image of all fs of being present in odd-multiple can further be weakened.Therefore, when the mixing multiphase filter 625 based on following equation [1] is applied to second phase (the above-mentioned phase place being different from direct DPA), this DAC image being present in fs odd-multiple can obtain weakening of essence and can ignore even in some cases.
[1] therefore, in certain embodiments, each delay path (that is h (n)) can play the effect of multiphase filter together with delay element 630.Therefore, its transfer function produced (from input x (n) to exporting y (n)) also comprises multiphase filter function.In the embodiment of the present invention, the benefit that such structure is brought is that the effect of this multiphase filtering can operationally clock frequency can not the basis of corresponding increase be achieved.In addition, when during when the restriction providing a specific clock frequency to be subject to technical matters and/or in high frequency of operation, power consumption is too high, such structure can bring significant advantage.In certain embodiments, when delay element 630 is applied to different paths, these delay elements 630 are equidistantly isolated, but in other embodiment, such setting not necessarily is required.As a rule, multiphase filter operates on numeric field completely, but it should be noted that, in some embodiments of the invention, this multiphase filter can be achieved by the mode of mixing, such as digit data stream is divided into different paths, then combines again in RF/ analog domain, thus to realize the function of multiphase filtering.
Although filter described is in embodiments of the present invention described to mix multiphase filter usually, but what those skilled in the art will envision that is, in other examples, other wave filter technology can be applied equally, roughly suppress DAC image with the odd-multiple in fs.
Above-mentioned mixing multiphase filter roughly can act as the multiphase filter that has the pure digi-tal of the input sample frequency of fs and the output sampling frequency rate of 2fs.The DAC image at all odd-multiple places in fs can be made retarded by the transfer function of the h (n) in the above-mentioned formula of careful design [1], x (n) to y (t).In this, mixing multiphase filter is the same with the above-mentioned performance with the multiphase filter of the pure digi-tal of the output sampling frequency rate of 2fs mentioned, its reason is, to be used owing to only there being a DPA in the multiphase filter of pure digi-tal and its enter code word operates on the sample frequency of 2fs, thus the multiphase filter of this pure digi-tal only can be observed under the multiple of 2fs, that is will not there is DAC image at the odd-multiple place of fs.In embodiments of the present invention, use this mixing multiphase filter advantage to be, the sample frequency of the enter code word of each DPA in two DPA is fs, instead of the sample frequency of the enter code word of an independent DPA is 2fs.
Refer to Fig. 7 now, Figure 7 shows that the simple structure schematic diagram of the RF transmitter 700 according to further embodiment of this invention, this RF transmitter 700 applies a digital pre-distortion code word 705 in the multiple phase places using polyhybird multiphase filter to arrange, for example, this RF transmitter can be implemented in the digital signal processing module 408 shown in Fig. 4.In the embodiment of the present invention, this digital pre-distortion code word 705 by a digital baseband element (not shown) by receiving multiple (IQ) input signal, and can perform conversion operations (such as performing map operation) to multiple (IQ) input signal that this receives and produces.This digital pre-distortion code word 705 directly can be provided to (710) first digital power amplifiers (DPA1) 715, this first digital power amplifier 715 can be such as a part for the PA module 530 shown in Fig. 5, comprises the high power analog conversion function to RF signal.
As shown in Figure 7, this digital pre-distortion code word 705 can also via mixing multiphase filter 725,745 and delay element 730 corresponding with it respectively, 750 are provided to multiple digital power amplifier (DPA2 respectively, DPAL) 735, in 755, to introduce each phase deviation in each signal path independent of each other.Therefore, in the present embodiment, 2 phase place implementations shown in Fig. 6 replace by leggy (L phase place) implementation.In this fashion, this mixing multiphase filter provides and is similar to the function that has the multiphase filter of the pure digi-tal of the input sample frequency of fs and the output sampling frequency rate of Lfs.By careful design h2 (n) ..., hL (n), x (n) can make the equal energy of the DAC image at all multiple places except the multiple of Lfs, almost fs retarded to the transfer function of y (t).This performance and the above-mentioned performance with the pure digi-tal multiphase filter of output sampling frequency rate Lfs mentioned are very similar, its reason is, to be used owing to only there being a DPA in the multiphase filter of pure digi-tal and sample frequency that its enter code word operates on Lfs also will be, therefore it only can be observed under the multiple of Lfs, that is at fs, 2fs, ... (L-1) fs, (L+1) fs, (L+2) fs, ..., all will not there is DAC image in the places such as (L+L-1) fs.
In the embodiment of the present invention, above-mentioned phase deviation equals T/L, and wherein T=1/fs, fs are the sample frequency of code word row x (n), and L is the number of the signal path (or filtered phase signal) of application mix multiphase filter.
From the first digital power amplifier 715, second digital power amplifier 735 ..., combiner 720 place that is output in of L digital power amplifier 755 is combined, and produces output 740 a to antenna (for illustrating).
The application of above-mentioned multiple mixing multiphase filter is similar with the application acting on the multiple digital multiphase filter in pure digi-tal territory.But this pure digi-tal multiphase filter with L phase place needs the clock frequency arranging its final digit code word to be Lfs.On the contrary, in the application of multiple mixing multiphase filters of the present embodiment shown in Fig. 7, the clock frequency of each digital word all can maintain fs.However, L bar digit data stream is still had to input in each DPA.The combination operation of this L bar digit data stream is executed in each DPA715,735,755 and combinational network 720 in and be not executed in numeric field.
By this mode, in the embodiment shown in Fig. 6 and Fig. 7 of the present invention, multiple digital filter was applied in multiple outs of phase of DPA by this RF transmitter before entering to analog domain in digital signal, thus provided a kind of L times linear interpolation DPA.In this fashion, by careful control/select this mixing multiphase filter 725 ..., 745 and delay element 730 ..., 750, the power DAC image of all fs of being present in odd-multiple can further be weakened.
Refer to Fig. 8 now, Figure 8 shows that the simple structure schematic diagram 800 of an embodiment of the power amplifier module 530 of Fig. 5.The orthogonal digital code word that this power amplifier module 530 exports for receiving digital signals processing module, and at least partly based on the orthogonal digital code word received (I-BB [12:0], Q-BB [12:0]) 512,514, export an analog rf signal 830 for by RF interface, such as, transmitted by the antenna 403 shown in Fig. 4.This power amplifier module 530 comprise have multiple ' first array (I-PA) 810 of I ' switch-mode-power unit 870, and there is second array (Q-PA) 820 of multiple ' Q ' switch-mode-power unit 870.This first array 810 for receiving at least part of first (homophase) digital word 512, and produces first (homophase) composition 832 of analog rf signal 830 at least partly based on the digital word 512 received.Second array 820 then for receiving at least part of second (orthorhombic phase) digital word 514, and produces second (orthorhombic phase) composition 834 of analog rf signal 830 at least partly based on this digital word 514 received.First (homophase) composition 832 and second (orthorhombic phase) composition 834 are then combined to produce analog rf signal 830.
Thus, by providing, there is multiple switch-mode-power cellular array 810,820 for the digital word 512 receiving each composition being respectively used to multidimensional signal (such as multiple (IQ) signal) respectively, 514, and produce the composition 832 after amplifying accordingly respectively, composition 832 after this amplification of 834(, 834 are combined subsequently), the power amplifier module 530 that one can be digitally controlled to produce multidimensional (such as IQ) amplifying signal is achieved.
In some embodiments of the invention, each of the switch module power cell 870 of above-mentioned array 810,820 can be used for receiving at least part of digital word 512,514 respectively, and this digital word 512,514 comprises N number of control bit.In addition, array 810, each of 820 can comprise N number of switch-mode-power unit, and each switch-mode-power unit 870 optionally exports a current signal (Iout) 874 for the value based on the control bit received.Every an array 810, the output of the switch-mode-power unit 870 in 820 is all coupled in together, thus every an array 810, the multiple power cell output current signals (Iout) 874 in 820 can be combined the constituent 832,834 providing analog rf signal 830 respectively.In certain embodiments, the output current signal (Iout) 874 of each switch-mode-power unit 870 can according to its each self-corresponding control bit by additional weight value.Thus, the array output current signal of every an array 810,820 will represent the numerical value of the digital word that it receives.
Analog conversion function can well be combined with power amplification function by the power amplifier module 530 shown in Fig. 8, thus simplifies the design of RF transmitter.In addition, the array 810,820 of the switch module power cell of separation can support I composition and the Q composition of multiple IQ input signal respectively, makes power amplifier module 530 more can be suitable for arrowband and wide-band modulation input signal simultaneously.
This in power amplifier module 530 shown in Fig. 8 has switch-mode-power cellular array 810,820 are also respectively used to reception carrier frequency signal 840,845, and at least partly based on receiving this carrier frequency signaling 840,845 to produce each composition 832,834 of analog rf signal 830 respectively.For example, this carrier frequency signaling 840,845 can be provided in each switch-mode-power unit 870 respectively, such as, 840 places in illustrated power cell 870.Therefore, a kind of 2 Selecting phasings are able to realize at analog domain, wherein can produce two groups of LO based on sign bit I-BB [12] (or sign bit Q-BB [12]).By together with all amplitude positions I-BB [11:0] (or Q-BB [11:0]) to open or close array 810(or array 820) in each switch-mode-power unit, this power amplifier module 530 shown in Fig. 8 can realize arbitrary in mixing function and power amplification function and analog conversion function or both combinations.The silicon area occupied by larger power and increase can be consumed to the wiring (routing) of two groups of LO.Thus, the power amplifier module 530 shown in Fig. 8 also can realize the combination of mixing function and power amplification function and analog conversion function.
In analog domain, realize 2 Selecting phasings with above-mentioned, and it is different to produce two groups of LO based on the value of sign bit, in other embodiment of the present invention, a kind of leggy can also be realized and select, wherein can produce based on one or more Selecting phasing position and organize LO more.
Optimally, due to numeric field is extended to power amplifier module 530, therefore without the need to arranging linear front wheel driving amplifier or baseband filter in circuit.In addition, the use of numerical control power cell also makes the power consumption of power amplifier module 530 can be roughly consistent with transient state RF power output.
Figure 9 shows that the simple structure schematic diagram of the RF transmitter 900 according to yet another embodiment of the invention, the digital pre-distortion code word 905 that wherein this RF transmitter 900 uses is applied in digital power amplifier by part interpolation (partialinterpolation), and this RF transmitter 900 such as can be implemented in the digital signal processing module 408 shown in Fig. 4.
In embodiments of the present invention, this digital pre-distortion code word 905 can receive multiple (IQ) signal of input by a digital baseband element (not shown), and changes (such as performing map operation) to multiple (IQ) signal of the input received and produce.
In one embodiment of the invention, only have the PA power cell of part to be implemented interpolation (interpolate) operation, namely first bit data flow is divided into the mulitpath with different delays, then merged again.Therefore, in the part interpolation embodiment shown in Fig. 9, first DPA is divided into two parts: ' DPAa ' 915 and ' DPAb1 ' 935 add the combination (various piece of the PA module 530 such as shown in Fig. 5, wherein this PA module 530 comprises the high power analog conversion function to RF signal) of ' DPAb2 ' 955.In the embodiment of the present invention, for the digital pre-distortion code word 905 that ' DPAa ' 915 uses, do not implement interpolation operation, such as ' DPAa ' receives control bit X [M:0], and meanwhile, for ' DPAb1 ' 935 and ' DPAb2 ' 955, then implement the interpolation operation to used digital pre-distortion code word and reception two groups of control words, such as it can be set to any one in application all-key word interpolation or partial codeword interpolation.
But, and the bit of not all implements interpolation operation, namely only performs interpolation to the part of control bit X [M:0].In the application of partial codeword interpolation, only interpolation is carried out to a part (X [I-1:0] in such as X [M:0]) for base band control bit.Therefore, the each several part interpolation 910 of digital pre-distortion code word 905 is applied to multiple (being two in the present embodiment) digital power amplifier 935 respectively, in 955, and this second path leading to ' DPAb2 ' 955 also by a delay element 930 to introduce multiple phase deviation respectively at the most in signal path.In embodiments of the present invention, this phase deviation can equal T/2, T=1/fs, and wherein fs is the sample frequency of codeword sequence x (n).
In the application of all-key word interpolation, input to ' DPAa ' 915 and be respectively X1 [M:0] and X2 [M:0] with the base band control word of ' DPAb1 ' 935, ' DPAb2 ' 955.
In the present embodiment, combiner 920 place that is output in of first ' DPAa ' 915 and the second ' DPAb1 ' 935, ' DPAb2 ' 955 is combined, and produces output 940 to an antenna (not shown).Such as, and in another embodiment, this second ' DPAb1 ' 935 and ' DPAb2 ' 955 can comprise mulitpath, ' L ' paths shown in Fig. 7, wherein every paths all comprises different delay skew T/L.
Therefore, summarize to the above embodiments, part interpolation can comprise two-layer implication: (i) the DPA unit of part controls by interpolation bit; (ii) only part interpolation operation is performed to part control bit.
By this mode, reduce although may introduce very little performance, the use of part interpolation can reduce DAC image, reduces circuit complexity and power consumption simultaneously.A basic object of interpolation operation is used also to comprise the lower clock frequency of maintenance.Therefore, optimally, although each path all has different clock delays, every paths all operates digital clock frequencies under identical clock frequency and total and can't increase.
Refer to Figure 10 now, Figure 10 shows that, according to the embodiment of the present invention, full interpolation 1000 or part interpolation 1050 are implemented to be applied to the comparison schematic diagram of two kinds of execution modes of DPA to DPD code word.In the present embodiment, DPA is set to comprise 32 system unit (32U) 1015, the weighted value of each unit of 1030(is ' 64 '), the weight of 31 each unit of a system unit (31U) 1020,1035(is ' 64 ') and 6 binary cells (6B) 1025, the weight of each unit of 1040(is respectively ' 32 ', ' 16 ', ' 8 ', ' 4 ', ' 2 ', ' 1 ').As shown in the figure, at a DPA(DPAa) 1005, in 1055, no matter for part interpolation 1050 or full interpolation 1000, input x1 (t) is all provided to 32U1015, in each of 31U1020 and 6B1025.In full interpolation application 1000, input x2 (t) can be provided to the 32U1030 of the 2nd DPA (DPAb) 1010, in each of 31U1035 and 6B1040.
But, DPA part interpolation application 1050 in, the 32U1030 being positioned at top does not perform interpolation, and input x1 (t) by bring up again be supplied to 32U1030 each in.Meanwhile, input x2 (t) and be provided to the 2nd DPA(DPAb) 31U1035 and 6B1040 of 1060 each in.
In the embodiment of the present invention, various part interpolation method can be used.Such as, in one embodiment, interpolation can be performed to amplitude controlling word, and in another embodiment, interpolation can be performed to sign bit, or in other embodiments, interpolation can also be performed to the arbitrary portion controlling code word.
Figure 11 shows that the simple structure schematic diagram of the RF transmitter 1100 going back an embodiment according to the present invention, wherein this RF transmitter 1100 simultaneously by mixing multiphase filter application DPD code word 1105 and applying portion interpolation in DPA, this RF transmitter 1100 such as can be implemented in the digital signal processing module 408 shown in Fig. 4.
In the embodiment of the present invention, this digital pre-distortion code word 1105 can receive multiple (IQ) signal of input by a digital baseband element (not shown), and changes (such as performing map operation) to multiple (IQ) signal of the input received and produce.
In the present embodiment, only interpolation operation is implemented to part PA power cell, therefore, in the part interpolation application shown in Figure 11, first DPA is split into two parts: ' DPAa ' 1115 and ' DPAb1 ' 1135 add the various piece of the PA module 530 of combination 1155(such as shown in Fig. 5 of ' DPAb2 ', and wherein this PA module 530 comprises the high power analog conversion function to RF signal).In one embodiment of the invention, for the digital pre-distortion code word 1105 that ' DPAa ' 1115 uses, do not implement interpolation operation, and meanwhile, for ' DPAb1 ' 1135 and ' DPAb2 ' 1155, be then set to apply in all-key word interpolation or partial codeword interpolation any one.
In the application of partial codeword interpolation, only interpolation operation is implemented to a part (X [I-1:0] in such as X [M:0]) for base band control bit.Therefore, the each several part interpolation 1100 of digital pre-distortion code word 1105 is provided to multiple (being two in the present embodiment) digital power amplifier 1135 respectively, in 1155, and this second path leading to ' DPAb2 ' 1155 also mixes one or more delay elements 1130 of multiphase filter (h (n)) 1145 and correspondence to introduce respectively in the phase deviation signal path that bar is independent at the most by one.In embodiments of the present invention, this phase deviation can be set to equal T/2, and wherein T=1/fs, fs are the sample frequency of codeword sequence x (n).In the embodiment of the present invention, this mixing multiphase filter h (n) 625 performs filter function with sample frequency fs.
In the application of all-key word interpolation, input to ' DPAa ' 1115 and be respectively X1 [M:0] and X2 [M:0] with the base band control word of ' DPAb1 ' 1135, ' DPAb2 ' 1155.
First ' DPAa ' 1115 and the second ' DPAb1 ' 1135, ' DPAb2 ', combiner 920 place that is output in of 1155 is combined, and produces output 1140 to an antenna (not shown).Such as, and in an alternative embodiment of the invention, this second ' DPAb ' 1135 and ' DPAb2 ' 1155 can comprise mulitpath, ' L ' paths shown in Fig. 7, wherein every paths all comprises different delay skew T/L.
In this fashion, by careful design mixing multiphase filter 1145 and delay element 1130, all power DAC images being present in the odd-multiple place of fs can further be slowed down.Therefore, when mixing shown in multiphase filter 1145(such as aforesaid equation [1]) when being applied to second phase, this DAC image being present in fs odd-multiple can obtain weakening of essence and can ignore even in some cases.
Thus, reduce although may introduce very little performance, the use of part interpolation can reduce DAC image, reduces circuit complexity and power consumption simultaneously.The basic object of of interpolation operation is used also to comprise the lower clock frequency of maintenance.Therefore, optimally, although each path all has different clock delays, every paths all operates digital clock frequencies under identical clock frequency and total and can't increase.
Figure 12 shows that the simple module schematic diagram of the RF transmitter 1200 according to further embodiment of this invention, wherein this RF transmitter 1200 simultaneously by mixing multiphase filter h (n) 1245 application DPD code word 1205 and applying portion interpolation in digital power amplifier, for example, this RF transmitter 1200 can be implemented in the digital signal processing module 408 shown in Fig. 4.
In the embodiment of the present invention, this digital pre-distortion code word 1205 can receive multiple (IQ) signal of input by a digital baseband element (not shown), and changes (such as performing map operation) to multiple (IQ) signal of the input received and produce.This DPD code word 1205 can directly (1210) be provided to a DPA(DPA1) in 1215, a DPA1215 can be such as a part for the PA module 530 shown in Fig. 5, wherein comprises the high power analog conversion function to RF signal.This DPD code word 1205 can also be provided to the 2nd DPA(DPA2 by a sign change function 1255) in 1215, with the sign bit using the sign bit in the first path to replace the second path.Thus, sign bit will be consistent by the sign bit in interpolation so that two paths, but remainder signal due to through a series of mixing multiphase filtering, delay and absolute value function to be provided to the 2nd DPA1235, therefore its signal is by different from the signal on above-mentioned first path.In this fashion, DPA code word 1205 will via mixing multiphase filter 1245 and delay element 1230 to be provided to the 2nd DPA1235, thus introduce a phase deviation in signal path, in the embodiment of the present invention, this phase deviation can be set to equal T/2, wherein T=1/fs, and fs is the sample frequency of codeword sequence x (n).And in the embodiment of the present invention, this mixing multiphase filter h (n) 1245 performs filter function with sample frequency fs.Filtered phase-shift signal was then input in an absolute value function 1250 to produce the absolute value of DPD code word before being provided to the 2nd DPA1235.
The output of the one DPA1215 and the 2nd DPA1235 is then combined in combiner 1220, and produces output valve 1240 to an antenna (not shown).It should be noted that the RF transmitter 1200 due to the present embodiment is a digital RF transmitter, therefore wherein do not comprise any Analog Baseband filter function.
Refer to Figure 13 now, Figure 13 shows that the simplified flow chart 1300 of the digital filtering method according to one embodiment of the invention, this digital filtering method is such as mixing multiphase filtering method, for minimizing DAC image.The method starts from step 1310, receives an input complex signal and produces at least one base band character signal accordingly.Then in step 1315, amplifying stage is divided into multiple part, wherein each part is controlled by one group of up-sampling baseband signal.Then, in step 1320, at least one base band character signal is applied in the first power cell of power amplifier module.Although not shown in fig. 13, this paths will comprise one or more digital filters or delay cell.Then in step 1325, the base band character signal after this up-sampling is divided and be applied in mulitpath, and wherein every paths all comprises a digital filter, and this digital filter is all weighted a suitable yield value.Then, in step 1330, the part that one or more path of carrying base band character signal is sampled the clock cycle postpones.And in step 1335, inhibit signal, baseband signal, character signal are applied in each amplifying unit/level respectively.In last step 1340 again, the exit point that is output in of each amplifying unit/level is combined.
Refer to Figure 14 now, what Figure 14 shows that foundation one embodiment of the invention performs part interpolation operation to reduce the quick-reading flow sheets schematic diagram 1400 of the impact/level method for distinguishing of DAC image to code word.As shown in the figure, the method starts from step 1410, receives an input complex signal and produces at least one base band character signal accordingly.Meanwhile, this signal obtains enable.Then, in step 1415, the power amplifier comprising multiple amplifying unit/level is split into multiple part.In the present embodiment, amplifying unit/level is split into ' A ' part and ' B ' part.In addition, ' B ' part can also Further Division be ' B1 ' subdivision and ' B2 ' subdivision, and wherein ' B1 ' subdivision and ' B2 ' subdivision are equal to each other.It should be noted that in other embodiment of the present invention, the various piece of amplifying unit/level also can be further divided into quantity more than 2 subdivision, and these subdivisions also can be unequal.Then in step 1420, apply at least one base band character signal in the first power cell of power amplifier module, and in step 1425, this base band character signal X [M:0] is split into two groups of part interpolated signal X [M:I] and X [I-1:0].But those skilled in the art it is to be appreciated that, in other embodiment of the present invention, this base band character signal X [M:0] can also be split into the part interpolated signal more than two groups equally, and in other embodiment of the present invention, this base band character signal X [M:0] can be split to mulitpath, wherein a paths does not perform interpolation and at least one path or mulitpath and performs interpolation, ' L ' paths such as shown in Fig. 7, wherein every paths all comprises different delay skew T/L.Then in step 1430, one or more path is delayed by, and in step 1435, uses signal group X [M:0] with enable ' A ' part and the suitable element in ' B1 ' subdivision.Then, in step 1440, use the combination of the delay of X [M:I] and X [I-1:0] with the suitable element in enable ' B2 ' subdivision.Finally, in step 1445, the exit point that is output in of each amplifying unit/level is combined.
Refer to Figure 15 now, Figure 15 shows that according to use digital filtering (such as mixing multiphase filtering) method and part interpolation method while one embodiment of the invention, to reduce the quick-reading flow sheets schematic diagram 1500 of the impact/level method for distinguishing of DAC image.The method starts from step 1510, receives an input complex signal and produces at least one base band character signal accordingly.Meanwhile, this signal obtains enable.Then, in step 1515, the power amplifier comprising multiple amplifying unit/level is split into multiple part.In the present embodiment, amplifying unit/level can be divided into ' A ' part and ' B ' part.In addition, ' B ' part can also Further Division be ' B1 ' subdivision and ' B2 ' subdivision, and wherein ' B1 ' subdivision and ' B2 ' subdivision are equal to each other in the present embodiment.But it should be noted that in other embodiment of the present invention, the various piece of amplifying unit/level also can be further divided into quantity more than 2 multiple subdivisions, and these subdivisions also can be unequal.Then, in step 1520, at least one base band character signal is applied in the first Power Amplifier Unit of power amplifier module.And in the embodiment of two Power Amplifier Unit, this at least one base band character signal is also applied to via a sign change function in the second Power Amplifier Unit of power amplifier module.Then in step 1525, from baseband signal X [M:0], Xa [M:0] and Xb [M:0] is produced respectively for each Power Amplifier Unit/level, wherein Xb [M:0] is such as, by producing the suitable digital filter gain of X [M:0] weighting one, providing the mixing multiphase filter of transfer function ' H '.Then in step 1530, one or more path is postponed, and in step 1535, uses Xa [M:0] with enable ' A ' part and the suitable element in ' B1 ' subdivision.In addition, in step 1540, use the combination of the delay of Xa [M:I] and Xb [I-1:0] with the suitable element in enable ' B2 ' subdivision.Finally, in step 1545, the exit point that is output in of each amplifying unit/level is combined to be provided to an antenna.
In the embodiment shown in fig. 5, digital-to-RF transmitter 500 comprises multiple (inphase/orthogonal phase) transmitter.But those skilled in the art are scrutable, the present invention can also be realized by the digital-to-RF transmitter of another form equally.
Figure 16 to 19 is depicted as the simple structure schematic diagram of the various digital-to-RF transmitters that can benefit from the embodiment of the present invention.For example, the embodiment of the present invention can also be implemented into Digital Polarity transmitter, or in mixing polar transmitter (the RF transmitter 1600 such as shown in Figure 16).In this example structure, AM [0] ..., the clock frequency of AM [N] can change according to one or more Technique dynamic aforesaid.
In addition, those skilled in the art are scrutable, and the present invention can also be implemented in another multiple (inphase/orthogonal phase) transmitter, such as, multiple (inphase/orthogonal phase) RFDAC transmitter 1700 shown in Figure 17.In this example structure, the clock frequency being provided to the digital word of digital to RF converter can change according to one or more Technique dynamic aforesaid.
In addition, those skilled in the art are scrutable equally, and the present invention can also be implemented into a digital inverse (out-phasing) transmitter, in such as, digital inverse structure 1800 shown in Figure 18.In this digital inverse transmitter, after this modulation arranged by digital control word, phase place input can change according to one or more Technique dynamic aforesaid.
In addition, those skilled in the art are scrutable equally, and the present invention can also be implemented into Linear Amplifer (LINC) transmitter of a use linear element, in such as, LINC transmitter 1900 shown in Figure 19.In this LINC transmitter embodiment, clock frequency and the changeable dynamic source voltage of phase place input after modulation can change according to one or more Technique dynamic aforesaid.
Although the present invention is described by the embodiment of above-mentioned various digital-to-RF transmitter, those skilled in the art are scrutable, and concept of the present invention also can be applied in other structure, to produce same effect.
Because illustrated model embodiment major part all can use electronic component well-known to those skilled in the art and circuit to realize, therefore in order to enable those skilled in the art better understand basic conception of the present invention and it does not produced to the teaching of mistake, further detailed details can not be carried out to it to this partial circuit in this article and describe.
Although the present invention discloses as above with preferred embodiment; so itself and be not used to limit the present invention; any person skilled in the art; without departing from the spirit and scope of the present invention; when doing a little change and retouching, the scope that therefore protection scope of the present invention ought define depending on claims of the present invention is as the criterion.
Those skilled in the art are scrutable is, herein to all logic modules be only do exemplary explanation and and unrestricted, in other embodiment, each logic module or circuit element in the mode merged or decompose, can be achieved by other the logic module or circuit element with identical function.Therefore, scrutable, structure described herein is only exemplary explanation, and other structures that in fact can realize said function also can be applicable in the present invention.
Although through some embodiments, present invention is described, and this also means the restriction to specific implementation form of the present invention.The claim of protection scope of the present invention only the application is limited.In addition, although a characteristic of the present invention only may be described in one embodiment, it will be understood by a person skilled in the art that the variant characteristic of embodiment described in each can be combined according to the present invention.In claim, " comprising " one word should be construed to " comprise but be not limited to ", it does not get rid of other elements or step of not listing in claim.
In addition, although method, element and step in the present invention are all listed individually, this multiple method, multiple element or multiple method step all can be achieved by such as a unit or a processor.In addition, although protect different qualities of the present invention in different claims, these characteristics also can combine, and the separately protected combination not between representing characteristic of different claims is infeasible and/or bad.Meanwhile, the restriction of the characteristic comprised described by claim not to the protection category of claim, the characteristic that this claim limits also can be applied in other claim in appropriate instances.
In addition, putting in order of each claim also not implies that each feature of the present invention must be performed according to this specific order, especially not implies that the step in the method that the present invention protects must be run according to order specific in claims.On the contrary, the step that each step also can be applicable to by other is run.In addition, herein unique does not get rid of multiple situations, and the word such as " ", " first ", " second " does not get rid of multiple situations yet.
Claims (18)
1. a radio frequency RF transmitter, is characterized in that, comprises:
Comprise the power amplifier of multiple Power Amplifier Unit;
At least one signal processing module, be coupled to this power amplifier, this at least one signal processing module comprises at least one digital pre-distortion assembly, for applying at least one digital pre-distortion code word to multiple Power Amplifier Unit, wherein this at least one digital pre-distortion code word is applied at least one of the plurality of Power Amplifier Unit via a digital filter; And
Combiner, combines to produce an analog rf signal to multiple outputs of the plurality of Power Amplifier Unit based at least one digital pre-distortion code word after digital filtering at least part of, and this analog rf signal is used for being transmitted by a RF interface,
Wherein, this at least one digital pre-distortion code word is generated by carrying out conversion operations at least one multiplexed input signal received by this at least one signal processing module, and this digital filter is multiphase filter or the filter using the simple scalar gain factor or multiple filter factor.
2. RF transmitter as claimed in claim 1, it is characterized in that, this at least one digital pre-distortion code word is applied at least one of the plurality of Power Amplifier Unit via this digital filter and a phase shift element.
3. RF transmitter as claimed in claim 1, is characterized in that, this at least one digital pre-distortion code word is during via multiple different digital filter, to be applied in the plurality of Power Amplifier Unit respectively multiple.
4. RF transmitter as claimed in claim 3, is characterized in that, this at least one digital pre-distortion code word is during via multiple different digital filter and multiple different phase deviation unit, to be applied in the plurality of Power Amplifier Unit respectively multiple.
5. RF transmitter as claimed in claim 1, is characterized in that, comprises the signal being about to be transmitted by this RF interface in this multiplexed input signal.
6. RF transmitter as claimed in claim 5, it is characterized in that, this power amplifier comprises two arrays be made up of this Power Amplifier Unit multiple respectively, the different constituents of each this this at least one multiplexed input signal of array received, generate the different constituents of this analog rf signal with correspondence.
7. RF transmitter as claimed in claim 1, is characterized in that, this at least one digital signal processing module also for:
Interpolation operation is implemented to a part for this at least one digital pre-distortion code word; And
The interpolation part exporting this at least one digital pre-distortion code word to the plurality of Power Amplifier Unit at least one in.
8. RF transmitter as claimed in claim 7, it is characterized in that, this at least one digital signal processing module is used for the non-interpolation part of this at least one digital pre-distortion code word to be applied in the Part I of at least one of the plurality of Power Amplifier Unit, and the sign modification result of the non-interpolation part of this at least one digital pre-distortion code word is applied in the Part II of at least one of the plurality of Power Amplifier Unit.
9. RF transmitter as claimed in claim 8, it is characterized in that, this at least one digital signal processing module is coupled to a sign bit functional module, the sign bit of this sign bit functional module for using the sign bit of this non-interpolation part to replace this interpolation part.
10. RF transmitter as claimed in claim 8, it is characterized in that, this at least one digital signal processing module is coupled to an absolute value functions, and this absolute value functions to be arranged in an interpolation path and for providing the absolute value of this predistortion code word to this Power Amplifier Unit.
11. RF transmitters as claimed in claim 1, is characterized in that, the plurality of Power Amplifier Unit forms the switch-mode-power cell array of power amplifier module.
12. RF transmitters as claimed in claim 1, is characterized in that, this RF transmitter is at least one in following collection: multiple RF digital to analog converter reflector, Digital Polarity transmitter, mixing polar transmitter, digital inverse transmitter, uses the Linear Amplifer transmitter of non-linear element.
13. 1 kinds of integrated circuit (IC)-components, is characterized in that, comprise:
At least one digital signal processing module, is coupled to a power amplifier, and this power amplifier comprises multiple Power Amplifier Unit, and wherein this at least one digital signal processing module comprises:
At least one digital pre-distortion assembly, for applying at least one digital pre-distortion code word to the plurality of Power Amplifier Unit, wherein this at least one digital pre-distortion code word is applied at least one of the plurality of Power Amplifier Unit via a digital filter; And
Combiner, combines to produce an analog rf signal to multiple outputs of the plurality of Power Amplifier Unit based at least one digital pre-distortion code word after digital filtering at least part of, and this analog rf signal is used for being transmitted by a RF interface,
Wherein, this at least one digital pre-distortion code word is generated by carrying out conversion operations at least one multiplexed input signal received by this at least one signal processing module, and this digital filter is multiphase filter or the filter using the simple scalar gain factor or multiple filter factor.
14. 1 kinds of methods for generation of the RF signal transmitted by RF interface, it is characterized in that, the method comprises:
At least one digital pre-distortion code word is produced by carrying out conversion operations at least one multiplexed input signal;
Apply in multiple Power Amplifier Unit of this at least one digital pre-distortion code word to power amplifier, wherein this at least one digital pre-distortion code word is applied at least one of the plurality of Power Amplifier Unit via a digital filter; And
At least partly based at least one digital pre-distortion code word after digital filtering, combine to produce this RF signal to multiple outputs of the plurality of Power Amplifier Unit,
Wherein, this digital filter is multiphase filter or the filter using the simple scalar gain factor or multiple filter factor.
15. 1 kinds of RF transmitters, is characterized in that, comprise:
Comprise the power amplifier of multiple Power Amplifier Unit;
At least one signal processing module, is coupled to this power amplifier, and this at least one signal processing module comprises at least one digital pre-distortion assembly, and this at least one digital pre-distortion assembly is used for:
At least one digital pre-distortion code word is divided into multiple path;
This at least one digital pre-distortion code word is exported in a Power Amplifier Unit of this power amplifier via the first path, wherein on this first path, interpolation operation is not implemented to this at least one digital pre-distortion code word;
Interpolation operation is implemented to this at least one digital pre-distortion code word at least one path outside this first path in the plurality of path, and the interpolation part exporting this at least one digital pre-distortion code word is in a part for another Power Amplifier Unit of this power amplifier;
Combiner, for at least part of this interpolation part based on this at least one digital pre-distortion code word, multiple outputs of the plurality of Power Amplifier Unit of this power amplifier are combined, to produce an analog rf signal, this analog rf signal is used for being transmitted by a RF interface
Wherein, this at least one digital pre-distortion code word is generated by carrying out conversion operations at least one multiplexed input signal received by this at least one signal processing module.
16. RF transmitters as claimed in claim 15, it is characterized in that, this at least one signal processing module is used for the non-interpolation part of this at least one digital pre-distortion code word to be applied in the Part I of at least one of the plurality of Power Amplifier Unit, and the sign modification result of the non-interpolation part of this at least one digital pre-distortion code word is applied in the Part II of at least one of the plurality of Power Amplifier Unit.
17. 1 kinds of integrated circuit (IC)-components, it is characterized in that, comprise at least one signal processing module and combiner, this at least one signal processing module is coupled to a power amplifier, this power amplifier comprises multiple Power Amplifier Unit, and wherein this at least one signal processing module comprises:
At least one digital pre-distortion assembly, for:
At least one digital pre-distortion code word is divided into multiple path;
This at least one digital pre-distortion code word is exported in a Power Amplifier Unit of this power amplifier via the first path, wherein on this first path, interpolation operation is not implemented to this at least one digital pre-distortion code word;
Interpolation operation is implemented to this at least one digital pre-distortion code word at least one path outside this first path in the plurality of path, and the interpolation part exporting this at least one digital pre-distortion code word is in a part for another Power Amplifier Unit of this power amplifier;
This combiner, for at least part of this interpolation part based on this at least one digital pre-distortion code word, multiple outputs of the plurality of Power Amplifier Unit of this power amplifier are combined, to produce an analog rf signal, this analog rf signal is used for being transmitted by a RF interface
Wherein, this at least one digital pre-distortion code word is generated by carrying out conversion operations at least one multiplexed input signal received by this at least one signal processing module.
18. for generation of the method for the RF signal transmitted by RF interface, and it is characterized in that, the method comprises:
At least one digital pre-distortion code word is produced by carrying out conversion operations at least one multiplexed input signal received;
Apply in multiple Power Amplifier Unit of this at least one digital pre-distortion code word to power amplifier, wherein, the step applied in multiple Power Amplifier Unit of this at least one digital pre-distortion code word to power amplifier comprises further:
At least one digital pre-distortion code word is divided into multiple path;
This at least one digital pre-distortion code word is exported in a Power Amplifier Unit of this power amplifier via the first path, wherein on this first path, interpolation operation is not implemented to this at least one digital pre-distortion code word;
Interpolation operation is implemented to this at least one digital pre-distortion code word at least one path outside this first path in the plurality of path, and the interpolation part exporting this at least one digital pre-distortion code word is in a part for another Power Amplifier Unit of this power amplifier; And
At least partly based on this interpolation part of this at least one digital pre-distortion code word, combine multiple outputs of the plurality of Power Amplifier Unit of this power amplifier, to produce an analog rf signal, this analog rf signal is used for being transmitted by a RF interface.
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| US201261740584P | 2012-12-21 | 2012-12-21 | |
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| US13/972,924 | 2013-08-22 | ||
| US13/972,924 US9813086B2 (en) | 2012-12-21 | 2013-08-22 | RF transmitter, integrated circuit device, wireless communication unit and method therefor |
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| CN103888155B true CN103888155B (en) | 2016-04-06 |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN101247153A (en) * | 2008-03-13 | 2008-08-20 | 中兴通讯股份有限公司 | Method for improving power amplifier efficiency and digital predistortion broadband communicator |
| CN102752246A (en) * | 2011-04-21 | 2012-10-24 | 联发科技（新加坡）私人有限公司 | RF transmitter, integrated circuit device, wireless communication unit and method therefor |
| EP2515445A1 (en) * | 2011-04-21 | 2012-10-24 | MediaTek Singapore Pte Ltd. | RF Transmitter and integrated circuit device |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101247153A (en) * | 2008-03-13 | 2008-08-20 | 中兴通讯股份有限公司 | Method for improving power amplifier efficiency and digital predistortion broadband communicator |
| CN102752246A (en) * | 2011-04-21 | 2012-10-24 | 联发科技（新加坡）私人有限公司 | RF transmitter, integrated circuit device, wireless communication unit and method therefor |
| EP2515445A1 (en) * | 2011-04-21 | 2012-10-24 | MediaTek Singapore Pte Ltd. | RF Transmitter and integrated circuit device |
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