CN103441771B - Linear phase correction method with broadband configurable channel - Google Patents

Linear phase correction method with broadband configurable channel Download PDF

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Publication number
CN103441771B
CN103441771B CN201310377537.5A CN201310377537A CN103441771B CN 103441771 B CN103441771 B CN 103441771B CN 201310377537 A CN201310377537 A CN 201310377537A CN 103441771 B CN103441771 B CN 103441771B
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phase
frequency
phase correction
signal
length
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CN103441771A (en
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于泉涛
孟桥
陈从颜
平劲松
唐歌实
陈略
李黎
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Southeast University
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Southeast University
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Abstract

The invention discloses a linear phase correction method with a broadband configurable channel. After the data broadband and center frequency information observed and stored by a system is obtained, multi-component sinusoidal signals which evenly cover the frequency band are generated, and phase information of a digital system channel is provided. According to the linear phase correction method, any phase correction signal can be configured in real time, the frequency spectra of the phase correction signals are pure, and a phase can be conveniently calculated. According to the linear phase correction method, due to the fact that the frequency, in a base band, of the phase correction signals is in the frequency doubling relation, after frequency conversion is carried out on the same local oscillator, the phase relations of the phase correction signals are relatively fixed, linear phase characteristics of the channel are conveniently corrected, and the accurate channel delay time is obtained.

Description

The linear phase bearing calibration of the configurable passage in broadband
Technical field
The present invention relates to the method for designing of the configurable linear phase correction signal generator in a kind of broadband, more specifically, relate to the method for designing of the configurable linear phase adjuster in broadband for radio receiving system.
Background technology
Radio receiving system, in communication and fields of measurement, often needs the phase-frequency characteristic knowing signalling channel.Under such as celestial radio observation mode, need channel time delay error, namely the phase characteristic of passage corrects.Correction signal is held in front of the receiver and is added, and extracts amplitude and the phase place change of phase correction signal, just can calculate the Time Delay of Systems of passage, and then revise the time delay value observed, obtain geometric delays value accurately in receiver rear end.
When detecting the phase-frequency characteristic of receiving system passage, in order to prevent the phase-frequency characteristic of passage from changing in time, must ensure to detect and carrying out with Signal reception simultaneously, namely phase correction signal being joined in Received signal strength.
Existing way is in Practical Project, hold the pulse train shaper of an increase high speed Schottky tube in front of the receiver, reference signal is provided by atomic clock, utilize the harmonic wave letter produced, producing width is the pulse train of musec order, frequency domain is exactly the comb signal of 1MHz of being separated by, is used in rear end correction signal.This way is three problems in Practical Project has: 1, and phase correction signal is not the point-frequency signal of standard, affect phase calculation precision; 2, the phase correction signal that pulse train shaper generates is fixing, and when narrower bandwidth is observed, possible data record bandwidth can not comprise the phase correction signal of multiple 1MHz of being separated by, and just can not play the effect of signalling channel phasing; 3, the high speed harmonic energy of pulse train shaper is less, require very high, and efficiency is lower to amplification below.
So need a kind of method can revising channel phases on digital acquisition system.The method ensures to provide the single frequency point signal that several accurate initial phase is identical, and according to the requirement observed, these single frequency point signal can appear in the bandwidth of needs collection, in the front end of digital system, namely and then after digital sampler, being added with sampled data, is the information of sampled data with digital phase correcting.
Summary of the invention
Technical problem: the object of this invention is to provide one and be applied in radio receiving system, in igh-speed wire-rod production line, realize the phasing of data channel, the linear phase bearing calibration of the configurable passage in broadband of the passage precise delay information of any observation simulation can be accurately provided.
Technical scheme: the linear phase bearing calibration of the configurable passage in broadband of the present invention, comprises the following steps:
1) the quantity N needing phase correction signal component in frequency band is determined;
2) according to system-clock rate f swith the minimum observation simulation bandwidth B of system requirements min, obtain calculated rate resolution ax f according to the following formula: obtain the length L:L=f of the look-up table of functions of multi-components sinusoidal signal according to the following formula s/ Δ f;
3) according to step 2) the length L of look-up table of functions that determines, generating N number of length is the consistent sinusoidal signal X of L, initial phase i, i=1,2 ... .N, sinusoidal signal X iin the length L of look-up table of functions, comprise i cycle, each cycle is L/i; By N number of SIN function X ibe added summation, obtain will stored in functional value;
4) first determining step 3) obtain will stored in the quantization digit of functional value, then to will stored in functional value quantize, by the functional value after quantizing stored in look-up table of functions;
5) according to the length L of look-up table of functions, calculated address is 1,2 ... .L phase accumulator;
6) base band frequency selector provides cumulative step-length to phase accumulator: the bandwidth B that system provides base band frequency selector to need by control bus, then calculates the cumulative step-length being supplied to phase accumulator according to the following formula:
λ=B/B min, wherein B minfor the minimum observation simulation bandwidth that receiver requires;
7) the cumulative step-length of the phase accumulator obtained according to step 6), under clock effect, SIN function look-up table produces multifrequency point baseband digital signal, then changes multifrequency point baseband digital signal into multifrequency point base-band analog signal by digital to analog converter;
8) according to the center frequency value f of the observation simulation of system requirements 0and bandwidth B, determine the frequency values f of up-conversion lO=f 0-B/2, generates up-conversion signal S under system clock effect lO, multifrequency point base-band analog signal step 7) obtained upconverts to the frequency band of observation, forms phase correction signal;
9) phase correction signal that step 8) is formed is coupled to antenna end.
In step 4) of the present invention, according to the requirement of system signal noise ratio, the quantization digit M of the SIN function of look-up table can be determined, utilizes formula to determine or according to the quantity of hardware resource, determine quantization digit M.Obtain the maximum of sum functions S (n) absolute value of step 3), by each numerical value of sum functions S (n) divided by this maximum, realize normalization.Normalized sum functions S (n) value is multiplied by 2 m-1-1, stored in look-up table of functions after rounding.
The object of the present invention is achieved like this, is applied in radio receiving system, completes writing of phase correction signal generator circuit and map at host computer, by the cloth line file generated, by control bus, is loaded into generation FPGA realizing baseband signal.The baseband digital signal generated by FPAG is after digital to analog converter conversion, and through simulation upconverter, the phase correction signal after up-conversion is coupled on antenna.Control command is also by control bus, the bandwidth sum center frequency information of observation can be transported to configurable phase correction signal generator.
The present invention is for obtaining the time delay of the passage of system neutral phase property, comprise have identical initial phase, the multi-components single-frequency point SIN function maker of frequency multiplication relation, the method for designing of the frequency selector of any frequency range of covering system arranged arbitrarily according to system requirements.The present invention, according to the band bandwidth of system requirements observational record and centre frequency, generates the phase correction signal covering corresponding band in real time
Beneficial effect: the present invention compared with prior art, has the following advantages:
1) the configurable phase correction signal Generator Design in broadband of the present invention can according to the number of the required precision determination correction signal component of Measurement channel phase characteristic; 2) can according to system requirements, setting frequency correction signal and the bandwidth covered; 3) only add phase correction information at required frequency band, efficiency is higher; 4) use multi-components sinusoidal signal as phase correction signal, Measurement channel phase characteristic precision is higher, and survey calculation simplifies.Under limited hardware resource, this method achieve higher frequency precision, the output of phase correction signal more flexibly, adapt to wireless band requirement.Phase place relative between phase correction signal component is accurate, phasing is realized more simple, calculates channel time delay more accurate.
Accompanying drawing explanation
Fig. 1 is the method for designing flow logic figure of phase corrector of the present invention;
Fig. 2 is the element of phase corrector of the present invention;
Fig. 3 is the structure function block diagram that phase corrector of the present invention is described;
Fig. 4 is the spectrogram that phase corrector of the present invention exports baseband phase correction signal;
Fig. 5 is the spectrogram of the phase corrector output phase correction signal of invention;
Embodiment
Below in conjunction with the detailed description of accompanying drawing to exemplifying application, method for designing of the present invention can be made better to be understood.
Fig. 1 is the method for designing flow chart of phase corrector of the present invention, describes the key step of method for designing.Fig. 3 is the block diagram of the configurable wideband phase correction signal generator that method for designing according to the present invention realizes.As shown in Figure 3, base-band signal frequency selector is comprised according to the digital controlled oscillator of realization of the present invention, phase accumulator, the look-up table of storage function value, digital to analog converter part, the frequency selector of up-conversion local oscillator, upconverter and phase correction signal is coupled to antenna merit close device.
Embodiment comprises the following steps:
1) in the present embodiment, first in order to the linear phase characteristic of a correction signal passage, need the sinusoidal phase correction signal being evenly distributed with 4 components in a frequency band, namely get N=4 inside the technical scheme first step.
2) the operating frequency f of the phase correction signal generator of the present embodiment s64MHz, the minimum bandwidth B that receiving system requires min50kHz, frequency resolution then the length L=f/ Δ f=6400 of look-up table of functions can just be determined.
3) according to the result of two steps before Fig. 1, multiple sine function is calculated.The frequency of these SIN function becomes frequency multiplication relation and has identical initial phase.Wherein each signal n=0,1,2 ..., L, i=1,2 ... .N, be that the sine function summation of 6400 obtains sum functions S (n) by these 4 length, S ( n ) = Σ i = 1 N X i ( n ) , n＝0,1,2…,L。
4) in the present embodiment, by sum functions S (n) normalization, be exactly by the maximum of sum functions divided by sum functions absolute value, obtain normalized sum functions S 1(n)=S (n)/max (| S (n) |).In the present embodiment, according to the signal to noise ratio requirement of receiver system, the quantified precision M of functional value can be decided to be 10, by normalized sum functions S 1n () is multiplied by 2 m-1-1=511, stored in the look-up table of functions of Fig. 3 after then rounding downwards.
5) according to step 2) the length L=6400 of look-up table of functions that determines, calculated address is 1,2 ... .6400 phase accumulator.
6) step-length of phase accumulator was calculated at the base band frequency selector of Fig. 3 according to observing bandwidth information B at that time.Due to that is during step-length λ=1, output signal to be frequency be respectively the sinusoidal signal of 10kHz, 20kHz, 30kHz, 40kHz and.Fig. 4 shows the relation of the multiple component frequencies of bandwidth sum baseband phase correction signal.Bandwidth B and λ have following proportionate relationship: λ=B/B min, which achieves the conversion of bandwidth sum step-length.Such as B=8MHz, step-length λ now=B/B min=160.
7) step value flows to phase accumulator, produces phase bit address and flows to look-up table of functions, obtain frequency and be respectively 1.6MHz, the digital baseband phase correction signal of 3.2MHz, 4.8MHz, 6.4MHz, again through the digital to analog converter of Fig. 3, obtain Analog Baseband phase correction signal.
8) during signal due to Digital Signal Processing below, to sampled signal use quadrature frequency conversion, after be that complex signal is processed, so to baseband phase correction signal up-conversion time, as shown in Figure 5, need the centre frequency f of the central region of baseband frequency spectrum to antenna receiving signal 0on, so the up-conversion frequency selector of Fig. 3 utilizes the data bandwidth B of system storage and the centre frequency f of antenna receiving signal 0, obtain the frequency f of up-conversion lO=f 0-B/2, obtains the local oscillation signal of up-conversion.Such as, the centre frequency f of the signal received at the X-wave band autenna of astronomical observation 0be 8400MHz, go out the local frequency f of up-conversion lO=f 0-B/2=8396MHz.The upconverter of Analog Baseband phase correction signal in Fig. 3 that digital to analog converter in Fig. 3 transforms, just obtains the phase correction signal of uniform fold system storage signal bandwidth.In the above example after up-conversion, generate frequency and be respectively 8397.6MHz, the phase correction signal of 8399.2MHz, 8400.8MHz, 8402.4MHz.
9) the analog high frequency merit in Fig. 3 is closed device and phase correction signal is coupled to antenna end, then the signal of antenna reception is just with phase correction information.

Claims (1)

1. a linear phase bearing calibration for the configurable passage in broadband, it is characterized in that, the method comprises the following steps:
1) the quantity N needing phase correction signal component in frequency band is determined;
2) according to system-clock rate f swith the minimum observation simulation bandwidth B of system requirements min, obtain calculated rate resolution according to the following formula obtain the length L:L=f of the look-up table of functions of multi-components sinusoidal signal according to the following formula s/ Δ f;
3) according to described step 2) the length L of look-up table of functions that determines, generating N number of length is the consistent sinusoidal signal X of L, initial phase i, i=1,2 ... .N, described sinusoidal signal X iin the length L of look-up table of functions, comprise i cycle, each cycle is L/i; By described N number of sinusoidal signal X ibe added summation, obtain will stored in functional value;
4) first determining step 3) obtain will stored in the quantization digit of functional value, then to will stored in functional value quantize, by the functional value after quantizing stored in look-up table of functions;
5) according to the length L of look-up table of functions, calculated address is 1,2 ..., the phase accumulator of L;
6) base band frequency selector provides cumulative step-length to phase accumulator: the bandwidth B that system provides base band frequency selector to need by control bus, then calculates the cumulative step-length being supplied to phase accumulator according to the following formula:
λ=B/B min, wherein B minfor the minimum observation simulation bandwidth that receiver requires;
7) according to step 6) the cumulative step-length of the phase accumulator that obtains, under clock effect, SIN function look-up table produces multifrequency point baseband digital signal, then changes described multifrequency point baseband digital signal into multifrequency point base-band analog signal by digital to analog converter;
8) according to the center frequency value f of the observation simulation of system requirements 0and bandwidth B, determine the frequency values f of up-conversion lO=f 0-B/2, generates up-conversion signal S under system clock effect lO, by described step 7) and the multifrequency point base-band analog signal that obtains upconverts to the frequency band of observation, forms phase correction signal;
9) by described step 8) phase correction signal that formed is coupled to antenna end.
CN201310377537.5A 2013-08-26 2013-08-26 Linear phase correction method with broadband configurable channel Expired - Fee Related CN103441771B (en)

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CN105553904B (en) * 2015-12-09 2019-01-15 西安星通通信科技有限公司 A kind of digital signal amplitude and phase calibration method and system

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