CN103368589B - Interference inhibition method, interference inhibition device and receiver - Google Patents
Interference inhibition method, interference inhibition device and receiver Download PDFInfo
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Abstract
The invention relates to an interference inhibition method, an interference inhibition device and a receiver. The interference inhibition method comprises receiving an interfered signal which include a useful signal and an interference signal; obtaining a frequency mixing signal by carrying out frequency mixing and low-pass filtering on the received interfered signal and a local oscillation signal of the receiver; obtaining a filtering signal by carrying out channel selecting filtering on the frequency mixing signal; calculating the signal to noise ratio of the filtering signal; and continuing to receive the interfered signal when the signal to noise ratio satisfies an acceptance requirement, or adjusting frequency of the local oscillation signal of the receiver and then continuing to receive the interfered signal when the signal to ratio does not satisfy the acceptance requirement. Whether to change the frequency of the local oscillation signal is determined by continuous detection of the signal to noise ratio of the filtering signal based on characteristic of signal inhibition of a channel selection filter, and the local oscillation signal is adjusted through an algorithm in the technical scheme of the invention to enable the frequency of a combined interference signal passing a down-conversion unit to be beyond the passband range of the channel selection filter, thereby inhibiting the interference signal.
Description
Technical field
The present invention relates to communication technical field, particularly a kind of disturbance restraining method, device and receiver.
Background technology
Receiver is the important composition unit in Modern Communication System, its Main Function be from space-reception to the electromagnetic wave of different frequency screen, extract useful signal and carry out frequency conversion, amplification, then give demodulator demodulation the baseband signal meeting the requirement of certain signal to noise ratio.The useful signal received in practical communication system is often fainter, and also have a lot of interference signals adjoint wherein, therefore, sensitivity and selectivity just become the leading indicator weighing receiver performance simultaneously.Existing receiver comprises three kinds: superheterodyne receiver, zero intermediate frequency reciver and low intermediate frequency receiver.
The useful signal that above-mentioned all kinds of receiver antenna receives generally has minimum channel width and higher frequency, need the high-frequency signal frequency reducing using frequency mixer to receive, carry out channel filtering, amplification and demodulation in IF-FRE, but this in turn introduces image signal interference.Particularly, if the frequency of the frequency of the first signal and secondary signal is distributed in the both sides of local oscillation signal frequency symmetrically, then after mixing, the frequency of the first signal and the frequency of secondary signal all will be shifted to same IF-FRE.If the first signal and secondary signal one of them be useful signal, another is interference signal, and so the frequency at interference signal place is just called the frequency of image signal, and this interference phenomenon after mixing is called that image signal disturbs.
Ieee standard 802.16e-2005 defines receiver requirement at 8.3.11 item, to the requirement that receiver mirror image suppresses be wherein: receiver should be able to provide the mirror image of minimum 60dB to suppress, and generation must be comprised in all conditions mirror of receiver radio frequency and intermediate frequency thereafter.Therefore, a major challenge of receiver radio frequency Front-end Design how to realize sufficiently high mirror image to suppress.The method of current extensive use is complex mixing system, by sinusoidal signal by a quadrature phase shifter, obtains two orthogonal local oscillation signals, sends into two frequency mixers respectively, thus obtain the intermediate-freuqncy signal of input signal after complex mixing.
For superheterodyne receiver, it needs the image-reject filter of a high quality factor.So-called quality factor are a kind of quality index of sign energy storage device (as inductance coil, electric capacity etc.), the same ratio of loss of energy weekly of resonant circuit stored energy.The quality factor of element are larger, the circuit formed with this element or the selectivity of network better.But this image-reject filter is difficult to realize in integrated circuits.
For zero intermediate frequency reciver, although it does not need image-reject filter, because local oscillation signal is identical with the centre frequency of useful signal, comparatively serious direct current problem can be produced after frequency mixer, and be difficult to filtering.
By contrast, low intermediate frequency receiver and zero intermediate frequency reciver form closer to, both differences are that the local oscillation signal that low intermediate frequency receiver adopts is different with useful signal centre frequency, there is less difference, this difference is generally at half channel width (BW, Band Width) between a channel width, i.e. BW/2 < f
iF< BW.Adopt the low intermediate frequency receiver of complex mixing technology effectively can suppress the interference of image signal, the direct current signal amplitude simultaneously exported is less, relatively easier filtering.Adopt low intermediate frequency receiver in the reception programme of therefore current mobile phone more.
But, inventor finds, because low intermediate frequency receiver have employed the aforementioned complex mixing technology with two signal path, signal path not mating in gain and phase place will inevitably be caused due to fabrication error, causing adopting the mobile phone of low intermediate frequency receiver scheme carrying out test certification and the decline of actual use medium sensitivity, even occurring call drop phenomenon.
More disturbance restraining methods about communication technical field can be the U.S. patent documents US2009010366A1 of " method and apparatus suppressing arrowband interference " (Method And Device For Suppressing Narrowband Interference) with reference to denomination of invention, but still do not solve the problem.
Summary of the invention
The problem that technical solution of the present invention solves adopts the receiver of complex mixing technology by the interference of outer signals in prior art, and sensitivity declines, and easily occurs call drop phenomenon.
For solving the problem, technical solution of the present invention provides a kind of disturbance restraining method, comprising:
Receive disturbed signal, described disturbed signal comprises useful signal and interference signal;
The local oscillation signal of the disturbed signal received and receiver is obtained mixed frequency signal after mixing and low-pass filtering treatment;
Described mixed frequency signal is carried out Channel assignment filtering and obtain filtering signal;
Calculate the signal to noise ratio of described filtering signal;
Receive requirement when described signal to noise ratio meets, continue to receive disturbed signal; Receive requirement when described signal to noise ratio does not meet, disturbed signal is received in the follow-up continued access of frequency of the local oscillation signal of adjustment receiver.
Alternatively, the frequency initial value of described local oscillation signal is set as centre frequency and the IF-FRE sum of useful signal.
Alternatively, described disturbed signal meets and receives the signal to noise ratio requiring to include described filtering signal and be greater than pre-determined threshold; The satisfied signal to noise ratio requiring to include described filtering signal that receives of described disturbed signal is less than described pre-determined threshold.
Alternatively, described pre-determined threshold is less than or equal to the demodulation threshold of baseband chip.
Alternatively, described when the satisfied reception requirement of described signal to noise ratio, the follow-up continued access of frequency of the local oscillation signal of adjustment receiver is received disturbed signal and is comprised: when described signal to noise ratio is less than described pre-determined threshold, if the frequency of current local oscillation signal is centre frequency and the IF-FRE sum of useful signal, be then the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal.
Alternatively, described when the satisfied reception requirement of described signal to noise ratio, the follow-up continued access of frequency of the local oscillation signal of adjustment receiver is received disturbed signal and is also comprised: when described signal to noise ratio is less than described pre-determined threshold, if the frequency of current local oscillation signal is the centre frequency of useful signal and the difference of IF-FRE, be then centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal.
Alternatively, the signal to noise ratio of the described filtering signal of described calculating comprises carries out channel estimating by described filtering signal after analog-to-digital conversion, and records signal to noise ratio.
Technical solution of the present invention also provides a kind of interference suppression equipment, comprising:
Signal receiving unit, for receiving disturbed signal, described disturbed signal comprises useful signal and interference signal;
Down-converter unit, obtains mixed frequency signal for the disturbed signal that received by described signal receiving unit and local oscillation signal after mixing and low-pass filtering treatment;
Filter unit, the mixed frequency signal for described down-converter unit being exported carries out Channel assignment filtering and obtains filtering signal;
Computing unit, for calculating the signal to noise ratio of described filtering signal;
Control unit, the signal to noise ratio for obtaining when described computing unit meets reception requirement, controls described signal receiving unit and continues to receive disturbed signal; The signal to noise ratio obtained when described computing unit does not meet reception requirement, controls described signal receiving unit and continue to receive disturbed signal after the frequency of adjustment local oscillation signal.
Alternatively, described control unit comprises:
First adjustment unit, for being less than described pre-determined threshold when described signal to noise ratio, and if the frequency of current local oscillation signal is centre frequency and the IF-FRE sum of useful signal, be the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal.
Alternatively, described control unit also comprises:
Second adjustment unit, for being less than described pre-determined threshold when described signal to noise ratio, and if the frequency of current local oscillation signal is the centre frequency of useful signal and the difference of IF-FRE, be centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal.
Alternatively, described computing unit comprises:
AD conversion unit, for being converted to digital signal by described filtering signal by analog signal;
Digital signal processing unit, for carrying out channel estimating to the filtering signal after described AD conversion unit conversion, and records the signal to noise ratio of described filtering signal.
Technical solution of the present invention also provides a kind of receiver, comprises above-mentioned interference suppression equipment.
Alternatively, described receiver also comprises local oscillator generating unit, and described local oscillator generating unit is connected to described down-converter unit and described control unit.
Relative to prior art, technical solution of the present invention has following beneficial effect: the characteristic suppressing signal based on channel selection filter, by constantly detecting the signal to noise ratio treating described filtering signal, judge whether the frequency changing local oscillation signal, and by the algorithm adjusting local oscillation signal frequency described in technical solution of the present invention, local oscillation signal is adjusted, the frequency of the combination interference signal through down-converter unit is dropped on outside the free transmission range of channel selection filter, thus suppressed.Also overcome in addition receiver due to the fabrication error of complex mixing system cannot completely filtering image signal interference shortcoming.Relative to the low intermediate frequency receiver of the local oscillation signal of existing employing fixed frequency, technical solution of the present invention enhances the suppression to interference signal, improves the antijamming capability of receiver.
Accompanying drawing explanation
Fig. 1 is the schematic flow sheet of the disturbance restraining method that the embodiment of the present invention provides;
Fig. 2 is a kind of low intermediate frequency receiver structural representation;
Fig. 3 is useful signal spectrum diagram before and after down-converter unit and channel selection filter;
Fig. 4 is that desirable channel selection filter is to the inhibitory action schematic diagram of combination interference signal;
Fig. 5 is the concrete structure schematic diagram of down-converter unit in Fig. 2;
Fig. 6 is the spectrum diagram of image signal;
Fig. 7 is the particular flow sheet of the disturbance restraining method that the embodiment of the present invention provides;
Fig. 8 is the structural representation of the interference suppression equipment that the embodiment of the present invention provides;
Fig. 9 is the structural representation of the receiver that the embodiment of the present invention provides.
Embodiment
For enabling above-mentioned purpose of the present invention, feature and advantage more become apparent, and are described in detail the specific embodiment of the present invention below in conjunction with accompanying drawing.Set forth detail in the following description so that fully understand the present invention.But the present invention can be different from alternate manner described here to implement with multiple, those skilled in the art can when without prejudice to doing similar popularization when intension of the present invention.Therefore the present invention is not by the restriction of following public embodiment.
For the problem of prior art, inventor, through research, provides a kind of disturbance restraining method, device and receiver.First the term that the present invention relates to is explained and illustrated below:
Channel width (BW): the difference referring to the highest frequency that channel can pass through and the low-limit frequency that this channel can pass through, is determined by the physical characteristic of channel.
Signal to noise ratio (signal-to-noise ratio, SNR): refer under defined terms, the ratio of the available power on transmission channel specified point and noise power.
Sensitivity: under the condition of satisfied regulation signal to noise ratio, the minimum levels that receiver can receive.
Intermediate frequency: the difference frequency that the centre frequency of useful signal and the frequency compounding of local oscillation signal produce.
Please refer to Fig. 1, Fig. 1 is the schematic flow sheet of the disturbance restraining method that the embodiment of the present invention provides.As shown in Figure 1, described disturbance restraining method comprises:
Step S1, receive disturbed signal, described disturbed signal comprises useful signal and interference signal;
Step S2, obtains mixed frequency signal by the local oscillation signal of the disturbed signal received and receiver after mixing and low-pass filtering treatment;
Step S3, carries out Channel assignment filtering and obtains filtering signal by described mixed frequency signal;
Step S4, calculates the signal to noise ratio of described filtering signal;
Step S5, receives requirement when described signal to noise ratio meets, and continues to receive disturbed signal; Receive requirement when described signal to noise ratio does not meet, disturbed signal is received in the follow-up continued access of frequency of the local oscillation signal of adjustment receiver.
Mixed frequency signal comprises combination useful signal and combination interference signal.Combination useful signal refers to the signal that useful signal exports after mixing and low-pass filtering treatment, and combination interference signal refers to the signal that interference signal exports after mixing and low-pass filtering treatment.
With specific embodiment, above-mentioned disturbance restraining method is elaborated below.Receiver described in the embodiment of the present invention is low intermediate frequency receiver.
Please refer to Fig. 2, Fig. 2 is a kind of low intermediate frequency receiver structural representation.Low intermediate frequency receiver 100 comprises antenna element 110, band pass filter 120, radio frequency chip 130, baseband chip 140.
Radio frequency chip 130 comprises low noise amplifier (the Low Noise Amplifier be connected with band pass filter 120, LNA) 131, the down-converter unit 132 be connected with described low noise amplifier 131, the first variable gain amplifier 133 be connected with described down-converter unit 132, the channel selection filter 134 be connected with described first variable gain amplifier 133, the second variable gain amplifier 135 be connected with described channel selection filter 134, the local oscillator generating unit 136 for generation of local oscillation signal be connected with described down-converter unit 132.
Baseband chip 140 comprises the analog to digital converter 141 be connected with the second variable gain amplifier 135 of described radio frequency chip 130, and the digital signal processing unit 142 be connected with described analog to digital converter 141.
It should be noted that, above-mentioned receiver structure is only for illustration of principle of the present invention, and in practical application, the structure of receiver may change, and such as, analog to digital converter 141 may be comprised in baseband chip 140, also may be comprised in radio frequency chip 130.
After the antenna element 110 of receiver gathers useful signal, described useful signal is sent to by the frequency component in a certain frequency range but the frequency component of other scopes is decayed to low-level band pass filter 120.If the centre frequency of useful signal is f
rX, because band pass filter 120 and desirable low noise amplifier 131 are all linear units, do not change the frequency of signal, so the frequency that useful signal arrives the input of down-converter unit 132 after band pass filter 120 and low noise amplifier 131 is still f
rX.In down-converter unit 132, the centre frequency of useful signal and the frequency compounding of local oscillation signal produce a difference frequency, this difference frequency and intermediate frequency.
Specifically, please refer to Fig. 3 and composition graphs 2, Fig. 3 is useful signal spectrum diagram before and after down-converter unit and channel selection filter.Useful signal and local oscillation signal export mixed frequency signal after down-converter unit 132, and channel selection filter 134 carries out Channel assignment filtering process to described mixed frequency signal.Before input down-converter unit 132, the part in band pass filter 120 filtering disturbed signal outside band pass filter 120 free transmission range.After down-converter unit 132, the centre frequency of useful signal is moved.
That desirable channel selection filter is to the inhibitory action schematic diagram of combination interference signal with reference to figure 4, Fig. 4.Interference signal exports combination interference signal after down-converter unit 132 shown in Fig. 3, if combination interference signal drops on outside channel selection filter 134 free transmission range, channel selection filter 134 can by combination interference target signal filter (as shown in the left diagram); If combination interference signal drops in channel selection filter 134 free transmission range, channel selection filter 134 cannot filtering combination interference signal (as shown at right).As described in the background art, suppressing to realize sufficiently high mirror image, in low intermediate frequency receiver, usually adopting complex mixing system.
In the present embodiment, described complex mixing system can adopt the structure of the down-converter unit shown in Fig. 5.Described down-converter unit 132 comprises the first signal transacting branch road and secondary signal process branch road.Described first signal transacting branch road comprises for the first frequency mixer 31A by the input signal of described down-converter unit and the first local oscillation signal Frequency mixing processing, first low pass filter 32A, and the phase-shift unit 33 that the signal phase shift-90 for being exported by described first low pass filter 32A is spent.Described secondary signal process branch road comprises for the second frequency mixer 31B by the input signal of described down-converter unit and the second local oscillation signal Frequency mixing processing, and the second low pass filter 32B.Described down-converter unit also comprises the superpositing unit 34 for the output signal of the second low pass filter 32B in the output signal of phase-shift unit 33 in the first signal transacting branch road and secondary signal process branch road being superposed, and the signal that described superpositing unit 34 exports is intermediate-freuqncy signal.It should be noted that the above-mentioned description to down-converter unit structure can not be used for limiting protection scope of the present invention, technical solution of the present invention is equally applicable to the down-converter unit that well known to a person skilled in the art other structures.
Those skilled in the art know, and frequency mixer is a kind of nonlinear device, and its frequency of oscillation produced is the linear combination of the integral multiple of two-way input vibration or signal frequency.Frequency is f
rFuseful signal and frequency be f
lOlocal oscillation signal input mixer after, the frequency of described mixer output signal is m × f
rF+ n × f
lO, m × f
rF-n × f
lO,-m × f
rF-n × f
lO,-m × f
rF+ n × f
lO, (m, n are positive integer).Composition graphs 3, its medium frequency is m × f by the first low pass filter 32A and the second low pass filter 32B
rF+ n × f
lOwith-m × f
rF-n × f
lOtarget signal filter.First signal transacting branch road will wherein be spent in a road signal phase shift-90, therefore the two paths of signals superposition of the first signal transacting branch road and secondary signal process branch road eliminates frequency for-m × f
rF+ n × f
lOsignal, only remaining frequency is m × f
rF-n × f
lOsignal.
Particularly, frequency is f
rFuseful signal cos (2 π f
rFt) can be expressed as
first local oscillation signal sin (2 π f
lOt) can be expressed as
second local oscillation signal cos (2 π f
lOt) can be expressed as
if the gain of the first frequency mixer 31A and the second frequency mixer 31B is a, the gain of the first low pass filter 32A and the second low pass filter 32B is b, and so the output signal of the first frequency mixer 31A is:
The output terminals A point signal of the first low pass filter 32A is:
The output signal of the second frequency mixer 31B is:
The output B point signal of the second low pass filter 32B is:
The signal that first low pass filter 32A exports phase shift-90 after phase-shift unit 33 is spent, and is equivalent to be multiplied by-j, obtains phase-shift unit 33 output C point signal:
The output signal of phase-shift unit 33 output B point and the output signal of the second low pass filter 32B output C point are added and obtain:
As can be seen here, two paths of signals superposition eliminates frequency for-m × f
rF+ n × f
lOsignal, only remaining frequency is m × f
rF-n × f
lOsignal.
Especially, for the interference of image signal, refer to Fig. 6, Fig. 6 is the spectrum diagram of image signal.Frequency is f
rFthe frequency of the image signal of useful signal is:
f
IM＝f
RX+2f
IF＝f
RX+2(f
LO-f
RX)＝2×f
LO-f
RF。
Investigate as m=n=1, useful signal obtains after down-converter unit process:
m×f
RF-n×f
LO＝f
RF-f
LO，
Image signal obtains after down-converter unit process:
m×f
IM-n×f
LO＝m×(2×f
LO-f
RF)-n×f
LO＝f
LO-f
RF。
Therefore the frequency of image signal after frequency mixer can by follow-up with f
rF-f
lOcentered by the low pass filter filtering of frequency.Namely image signal is as the interference signal of characteristic frequency, ideally, can be suppressed completely by down-converter unit.
But inventor finds, adopt the mobile phone of low intermediate frequency receiver scheme carrying out in test certification and actual use, mobile phone is by the interference of outer signals, and sensitivity can decline, and even occurs call drop phenomenon.Analyze reason, mainly contain two aspects, one is interference signal output frequency after frequency mixer, low pass filter is m × f
inter-n × f
lOthe interference signal of (m, n are positive integer) drops in channel selection filter passband just, and filter cannot be leached, and causes receptivity to worsen.Another kind is because the amplitude of the gain of down-converter unit two branch roads in practice, local oscillator is not quite identical, and two local oscillators neither fine phase difference 90 degree, so image frequency still has a small amount of residual after frequency mixer and low pass filter.Interference signal output frequency after frequency mixer, low pass filter is n × f
lO-m × f
interthe interference signal of (m, n are positive integer) drops in channel filter pass band just, and filter cannot be leached, and causes receptivity to worsen.
Such as, f is worked as
inter=k × (f
rX+ f
iF)+Δ f
1, f
lO=f
rX+ f
iF, wherein, f
interrepresent the frequency of interference signal, f
rXrepresent the centre frequency of useful signal, f
lOrepresent the frequency of local oscillation signal, f
iFrepresent IF-FRE.For the ease of analyzing, suppose that channel selection filter 134 is desirable band pass filters, pass band width is BW, and the signal beyond passband is completely suppressed.
Composition graphs 2, works as m=1, n=k,
The frequency of the combination interference signal that down-converter unit 132 exports is:
m×f
inter-n×f
LO＝k×(f
RX+f
IF)+Δf
1-k×(f
RX+f
IF)＝Δf
1(1)
Or
-m × f
inter+ n × f
lO=-k × (f
rX+ f
iF)-Δ f
1+ k × (f
rX+ f
iF)=-Δ f
1(2) if
the frequency Δ f of the combination interference signal of above-mentioned formula (1)
1drop in the passband of channel selection filter.If
frequency-Δ the f of the combination interference signal of above-mentioned formula (2)
1drop in the passband of channel selection filter.In above-mentioned two situations, as long as interference signal is enough strong, will causes baseband signal signal-to-noise ratio degradation, cause sensitivity to decline, error code increases sharply, even call drop.
As previously mentioned, how to suppress the combination interference signal dropped in channel selection filter free transmission range, the antijamming capability improving receiver is problem demanding prompt solution of the present invention.Based on this, inventor considers, calculates the signal to noise ratio of the signal after mixing and filtering process of disturbed signal described in each receiving slot, and judges whether according to described signal to noise ratio the frequency changing local oscillation signal, to strengthen the suppression to combination interference signal, improve the antijamming capability of receiver.
Please refer to Fig. 7 and the particular flow sheet of the disturbance restraining method that composition graphs 1, Fig. 7 is the embodiment of the present invention to be provided.
Particularly, first perform step S1, receive disturbed signal, described disturbed signal comprises useful signal and interference signal.The centre frequency of described useful signal is f
rX, the frequency of described interference signal is f
inter, f
inter=k × f
rX+ Δ f, Δ f > 0.
In the present embodiment, the detailed process performing step S1 is as follows: during start, the frequency initial value of described local oscillation signal is set as centre frequency and IF-FRE sum, the i.e. f of useful signal
lO=f
iF+ f
rX.Wherein, Δ f > 0,
k > 1, and k is integer, BW represents the channel width of channel selection filter.Afterwards, receiver starts to receive disturbed signal.
Continue to perform step S2, the local oscillation signal of the disturbed signal received and receiver is obtained mixed frequency signal after mixing and low-pass filtering treatment.
According to the definition of aforementioned intermediate frequency, in frequency mixer, the centre frequency f of useful signal
rXwith the frequency f of local oscillation signal
lOmixing generation difference frequency, this difference frequency and intermediate frequency, with-f
iFrepresent, the definition of above-mentioned intermediate frequency can be formulated as f
lO-f
rX=f
iF.Therefore, after down-converter unit Frequency mixing processing:
F
rX'=f
rX-f
lO=f
rX-(f
rX+ f
iF)=-f
if, wherein, f
rXthe combination useful signal that the centre frequency of ' expression useful signal and local oscillation signal frequency export after down-converter unit;
f
IM1＝-f
RX+f
LO＝-f
RX+(f
RX+f
IF)＝f
IF，
Wherein, f
iM1represent that the amplitude due to the fabrication error gain of two signal transacting branch roads of down-converter unit in practice, local oscillation signal is not quite identical, to cause under nonideality the frequency that outputs signal after down-converter unit Frequency mixing processing of the image signal that remains, again, the free transmission range of channel selection filter is
therefore frequency can be f by channel selection filter
iM1target signal filter.
The frequency of the combination interference signal of the frequency of the residual interference signal except image signal and the frequency composition of local oscillation signal k subharmonic is:
f
inter-k×f
LO＝(k×f
RX+Δf)-k×(f
RX+f
IF)＝Δf-k×f
IF(3)
-f
inter+k×f
LO＝-(k×f
RX+Δf)+k×(f
RX+f
IF)＝k×f
IF-Δf (4)
Continue to perform step S3, described mixed frequency signal is carried out Channel assignment filtering and obtain filtering signal.Particularly, by described mixed frequency signal input channel selective filter, after filtering process, by the output output filtering signal of channel selection filter.
The free transmission range of channel selection filter
If above-mentioned formula (3) meets
Then this frequency component cannot by channel selection filter filtering.If above-mentioned formula (4) meets
Then this frequency component cannot by channel selection filter filtering.
Continue to perform step S4, calculate the signal to noise ratio of described filtering signal.The signal to noise ratio of the described filtering signal of described calculating comprises carries out channel estimating by described filtering signal after analog-to-digital conversion, and records signal to noise ratio.
Continue to perform step S5, receive requirement when described signal to noise ratio meets, continue to receive disturbed signal; Receive requirement when described signal to noise ratio does not meet, disturbed signal is received in the follow-up continued access of frequency of the local oscillation signal of adjustment receiver.Described disturbed signal meets and receives the signal to noise ratio requiring to include described filtering signal and be greater than pre-determined threshold; The satisfied signal to noise ratio requiring to include described filtering signal that receives of described disturbed signal is less than described pre-determined threshold.In addition, can according to the actual requirements, the signal to noise ratio setting described filtering signal equals pre-determined threshold and requires or do not meet to receive requirement as meeting to receive.Described pre-determined threshold is associated with the demodulation threshold of baseband chip.Demodulation threshold refers to that the signal that receiver receives should be not less than a certain threshold value under certain error rate prerequisite, the signal that the correct demodulation of receiver ability receives.The value of described pre-determined threshold is less than or equal to the demodulation threshold of described baseband chip usually, as when as described in demodulation threshold be 6dB time, the scope of described pre-determined threshold can be 1dB to 6dB, such as 3dB, 4dB or 5dB.
In the present embodiment, described when the satisfied reception requirement of described signal to noise ratio, the follow-up continued access of frequency of the local oscillation signal of adjustment receiver is received disturbed signal and is comprised: when described signal to noise ratio is less than described pre-determined threshold, if the frequency of current local oscillation signal is centre frequency and the IF-FRE sum of useful signal, be then the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal.
Particularly, as SNR < T, if f
lO=f
rX+ f
iF, then the frequency of local oscillation signal is pressed following formula adjustment: f
lO'=f
rX-f
iF, wherein, SNR represents signal to noise ratio, and T represents pre-determined threshold, f
lO' represent the frequency of local oscillation signal after this adjustment.
After the frequency adjustment of local oscillation signal, through down-converter unit process, wherein:
f
RX1＝f
RX-f
LO′＝f
RX-(f
RX-f
IF)＝f
IF，
F
rX1after representing the frequency adjustment of this local oscillation signal, the combination useful signal that the centre frequency of useful signal and the frequency of local oscillation signal export after down-converter unit;
f
IM2＝-f
RX+f
LO′＝-f
RX+(f
RX-f
IF)＝-f
IF，
F
iM2after representing the frequency adjustment of this local oscillation signal, because the amplitude of the fabrication error gain of two signal transacting branch roads of down-converter unit in practice, local oscillation signal is not quite identical, to cause under nonideality the frequency that outputs signal after down-converter unit Frequency mixing processing of the image signal that remains, again, now the free transmission range of channel selection filter is
therefore frequency can be f by channel selection filter
iM2target signal filter.
The frequency that the frequency of the residual interference signal except image signal and local oscillation signal increase the combination interference signal of wave frequency composition for k time is:
f
inter-k×f
LO′＝(k×f
RX+Δf)-k×(f
RX-f
IF)＝Δf+k×f
IF(5)
-f
inter+k×f
LO′＝-(k×f
RX+Δf)+k×(f
RX-f
IF)＝-Δf-k×f
IF(6)
Investigating above formula (5), because Δ f > 0, k > 1, and is integer, so obtain:
Δf+k×f
IF＞k×f
IF≥2×f
IF(7)
Again because
Composite type (7) can obtain:
Composition graphs 4 again, now the free transmission range of channel selection filter is
because frequency can be f by channel selection filter
iM2the residual components filtering of image signal, and remaining combination interference signal is positioned at the free transmission range of channel selection filter
outside, suppose that channel selection filter is ideal filter, namely can whole filtering the signal beyond passband.So the combination interference signal of above formula (5) can by channel selection filter filtering.
Investigate above formula (6) again, known-Δ f-k × f
iF< 0, because
So
Comprehensively can obtain:
Also namely now remaining combination interference signal is positioned at the free transmission range of channel selection filter
outside, so the combination interference signal of above formula (6) can by channel selection filter filtering.
According to above-mentioned analysis, as SNR < T, if f
lO=f
rX+ f
iF, then the frequency of local oscillation signal is pressed f
lO'=f
rX-f
iFadjustment, can make, beyond the frequency translation of combination interference signal to the free transmission range of channel selection filter, namely to inhibit the interference signal in received disturbed signal to a greater extent.
In the present embodiment, requirement is received when described signal to noise ratio does not meet, the follow-up continued access of frequency of the local oscillation signal of adjustment receiver is received disturbed signal and is also comprised: when described signal to noise ratio is less than described pre-determined threshold, if the frequency of current local oscillation signal is the centre frequency of useful signal and the difference of IF-FRE, be then centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal.
Concrete analysis, if the frequency of interference signal changes, f
inter=k × f
rX+ Δ f, Δ f < 0, then the frequency of formula (5), (6) may at channel selection filter passband
in scope, interference is formed to useful signal, causes SNR to decline.As SNR < T, if f
lO'=f
rX-f
iF, then the frequency of local oscillation signal is pressed following formula adjustment: f
lO"=f
rX+ f
iF, wherein, SNR represents signal to noise ratio, and T represents pre-determined threshold, f
lO" represent the frequency of the local oscillation signal after this adjustment.
Local oscillation signal frequency adjustment after, disturbed signal through down-converter unit Frequency mixing processing, wherein:
f
RX3＝f
RX-f
LO″＝f
RX-(f
RX+f
IF)＝-f
IF，
F
rX3after representing the frequency adjustment of this local oscillation signal, the combination useful signal that the centre frequency of useful signal and local oscillation signal frequency export after down-converter unit;
f
IM3＝-f
RX+f
LO＝-f
RX+(f
RX+f
IF)＝f
IF，
F
iM3after representing the frequency adjustment of this local oscillation signal, because the amplitude of the fabrication error gain of two signal transacting branch roads of down-converter unit in practice, local oscillation signal is not quite identical, to cause under nonideality the frequency that outputs signal after down-converter unit Frequency mixing processing of the image signal that remains, again, now the free transmission range of channel selection filter is
frequency can be f by channel selection filter
iM3target signal filter.
The frequency of the combination interference signal of the frequency of the residual interference signal except image signal and the frequency composition of local oscillation signal k subharmonic is:
f
inter-k×f
LO＝(k×f
RX+Δf)-k×(f
RX+f
IF)＝Δf-k×f
IF(8)
-f
inter+k×f
LO＝-(k×f
RX+Δf)+k×(f
RX+f
IF)＝k×f
IF-Δf (9)
Just wherein Δ f < 0.
Investigation formula (8) because Δ f < 0, k > 1, and is integer,
can obtain:
And now the free transmission range of channel selection filter is
suppose that channel selection filter is ideal filter, namely can whole filtering the signal beyond passband.
So the combination interference signal of formula (8) can by channel selection filter filtering.
Investigate formula (9) again, known k × f
iF-Δ f > 0,
Because
So
Comprehensively can obtain:
So the combination interference signal of formula (9) can by channel selection filter filtering.
It should be noted that and not all will use two kinds of local oscillation signal methods of adjustment above-mentioned in the present embodiment (frequency setting by local oscillation signal is the centre frequency of useful signal and the difference of IF-FRE and is centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal).If after the frequency of certain adjustment local oscillation signal, be such as after the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal, if the disturbed signal received afterwards meets through the signal to noise ratio of the filtering signal of mixing and filtering gained receive requirement always, then need not adjust the frequency of local oscillation signal, namely not needing is centre frequency and the IF-FRE sum of useful signal again by the frequency setting of local oscillation signal again.
Interference signal described in embodiment of the present invention can well known to a person skilled in the art noise source from any, as thermal noise, element noise or ambient noise etc.In the present embodiment, situation near the integral multiple specifically appearing at useful signal frequency with the frequency of interference signal is described, it should be noted that, disturbance restraining method described in embodiment of the present invention is not confined to the frequency being suitable for interference signal in the present embodiment, for all possible interference signal frequency, the disturbance restraining method in all applicable embodiment of the present invention.
Please refer to Fig. 8, Fig. 8 is the structural representation of the interference suppression equipment that the embodiment of the present invention provides.Technical solution of the present invention also provides a kind of interference suppression equipment, comprising:
Signal receiving unit 1, for receiving disturbed signal, described disturbed signal comprises useful signal and interference signal.
Down-converter unit 3, disturbed signal and local oscillation signal for being received by described signal receiving unit 1 superpose the mixed frequency signal of acquisition after mixing and low-pass filtering treatment.
Filter unit 4, the mixed frequency signal for described down-converter unit 3 being exported carries out Channel assignment filtering and obtains filtering signal.
Computing unit 5, for calculating the signal to noise ratio of described filtering signal.
Control unit 6, the signal to noise ratio for obtaining when described computing unit 5 meets reception requirement, controls described signal receiving unit 1 and continues to receive disturbed signal; The signal to noise ratio obtained when described control unit 5 does not meet reception requirement, controls described signal receiving unit 1 and continue to receive disturbed signal after the frequency of adjustment local oscillation signal.
The initial value of described local oscillation signal is set as centre frequency and the IF-FRE sum of useful signal.
The described signal to noise ratio that described computing unit 5 obtains meets and receives the signal to noise ratio requiring to include described filtering signal and be greater than pre-determined threshold; The satisfied signal to noise ratio requiring to include described filtering signal that receives of the described signal to noise ratio that described computing unit 5 obtains is less than described pre-determined threshold.Described pre-determined threshold is associated with the demodulation threshold of baseband chip.Demodulation threshold refers to that the signal that receiver receives should be not less than a certain threshold value under certain error rate prerequisite, the signal that the correct demodulation of receiver ability receives.The value of described pre-determined threshold is less than the demodulation threshold of described baseband chip usually, as when as described in demodulation threshold be 6dB time, the scope of described pre-determined threshold can be 1dB to 6dB, as 3dB, 4dB or 5dB.
Described computing unit 5 comprises:
AD conversion unit, for being converted to digital signal by described filtering signal by analog signal.
Digital signal processing unit, for carrying out channel estimating to the filtering signal after described AD conversion unit conversion, and records the signal to noise ratio of described filtering signal.
In the present embodiment, described digital signal processing unit can comprise:
Channel estimating unit (not shown), for estimating channel model parameters based on the filtering signal changed through described AD conversion unit, determines channel model.
Snr computation unit (not shown), for calculating the signal to noise ratio of described filtering signal based on described channel model.
Described control unit 6 comprises:
First adjustment unit, for being less than described pre-determined threshold when described signal to noise ratio, and if the frequency of current local oscillation signal is centre frequency and the IF-FRE sum of useful signal, be the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal.
In the present embodiment, described control unit 6 also comprises:
Second adjustment unit, for being less than described pre-determined threshold when described signal to noise ratio, and if the frequency of current local oscillation signal is the centre frequency of useful signal and the difference of IF-FRE, be centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal.
Described signal receiving unit can comprise: antenna, band pass filter and low noise amplifier.
Described interference suppression equipment can also comprise the first variable gain amplifier (not shown), before receiving mixed frequency signal at filter unit 4, makes gain process to described mixed frequency signal.Described first variable gain amplifier can be integrated in down-converter unit or filter unit.
Described interference suppression equipment can also comprise the second variable gain amplifier (not shown), for before computing unit 5 obtains filtering signal, makes gain process to described filtering signal.Described first variable gain amplifier can be integrated in filter unit or computing unit.
Please refer to Fig. 9, technical solution of the present invention also provides a kind of receiver 200, comprises interference suppression equipment described in above-described embodiment.Receiver 200 also comprises local oscillator generating unit 2, and described local oscillator generating unit 2 is connected to described down-converter unit 3 and described control unit 6.Receiver 200 receives disturbed signal by the signal receiving unit 1 in interference suppression equipment.Disturbed signal and local oscillation signal output filtering signal after down-converter unit 3 and filter unit 4 process.If the signal to noise ratio that computing unit 5 calculates filtering signal is less than pre-determined threshold, then interference suppression equipment adjusts the frequency of the local oscillation signal that local oscillator generating unit 2 produces by its control unit 6, continues to receive disturbed signal.The local oscillation signal that now local oscillator generating unit 2 exports to down-converter unit 3 changes, and the frequency of the combination interference signal exported through down-converter unit is dropped on outside the channel selection filter free transmission range of filter unit 4, thus by filtering.
Relative to existing receiver, the receiver of technical solution of the present invention can calculate signal to noise ratio based on received disturbed signal, to regulate the frequency of local oscillation signal adaptively, by the frequency translation of combination interference signal that drops in channel selection filter passband to outside this passband, also overcome in addition receiver due to the fabrication error of complex mixing system cannot completely filtering image signal interference shortcoming, effectively improve the antijamming capability of low intermediate frequency receiver.
In sum, the disturbance restraining method that the embodiment of the present invention proposes, device and receiver suppress the characteristic of signal based on channel selection filter, by constantly detecting the signal to noise ratio of signal to be demodulated, judge whether the frequency changing local oscillation signal, and by the algorithm adjusting local oscillation signal frequency described in technical solution of the present invention, local oscillation signal is adjusted, the frequency of the combination interference signal through down-converter unit is dropped on outside the free transmission range of channel selection filter, thus suppressed.Also overcome in addition receiver due to the fabrication error of complex mixing system cannot completely filtering image signal interference shortcoming.Relative to the low intermediate frequency receiver of existing employing fixed frequency local oscillator, technical solution of the present invention adds the suppression to interference signal, improves the antijamming capability of receiver.
Although the present invention with preferred embodiment openly as above; but it is not for limiting the present invention; any those skilled in the art without departing from the spirit and scope of the present invention; the Method and Technology content of above-mentioned announcement can be utilized to make possible variation and amendment to technical solution of the present invention; therefore; every content not departing from technical solution of the present invention; the any simple modification done above embodiment according to technical spirit of the present invention, equivalent variations and modification, all belong to the protection range of technical solution of the present invention.
Claims (16)
1. a disturbance restraining method, is characterized in that, comprising:
Receive disturbed signal, described disturbed signal comprises useful signal and interference signal;
The local oscillation signal of the disturbed signal received and receiver is obtained mixed frequency signal after mixing and low-pass filtering treatment;
Described mixed frequency signal is carried out Channel assignment filtering and obtain filtering signal;
Calculate the signal to noise ratio of described filtering signal;
Receive requirement when described signal to noise ratio meets, continue to receive disturbed signal; Receive requirement when described signal to noise ratio does not meet, disturbed signal is received in the follow-up continued access of frequency of the local oscillation signal of adjustment receiver; Wherein, the local oscillation signal of described adjustment receiver is: be the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal and/or be centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal.
2. disturbance restraining method according to claim 1, is characterized in that, the frequency initial value of described local oscillation signal is set as centre frequency and the IF-FRE sum of useful signal.
3. disturbance restraining method according to claim 1, is characterized in that, described disturbed signal meets and receives the signal to noise ratio requiring to include described filtering signal and be greater than pre-determined threshold; The satisfied signal to noise ratio requiring to include described filtering signal that receives of described disturbed signal is less than described pre-determined threshold.
4. disturbance restraining method according to claim 3, is characterized in that, described pre-determined threshold is less than or equal to the demodulation threshold of baseband chip.
5. disturbance restraining method according to claim 3, it is characterized in that, described when the satisfied reception requirement of described signal to noise ratio, the follow-up continued access of frequency of the local oscillation signal of adjustment receiver is received disturbed signal and is comprised: when described signal to noise ratio is less than described pre-determined threshold, if the frequency of current local oscillation signal is centre frequency and the IF-FRE sum of useful signal, be then the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal.
6. disturbance restraining method according to claim 5, it is characterized in that, described when the satisfied reception requirement of described signal to noise ratio, the follow-up continued access of frequency of the local oscillation signal of adjustment receiver is received disturbed signal and is also comprised: when described signal to noise ratio is less than described pre-determined threshold, if the frequency of current local oscillation signal is the centre frequency of useful signal and the difference of IF-FRE, be then centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal.
7. disturbance restraining method according to claim 1, is characterized in that, the signal to noise ratio of the described filtering signal of described calculating comprises carries out channel estimating by described filtering signal after analog-to-digital conversion, and records signal to noise ratio.
8. an interference suppression equipment, is characterized in that, comprising:
Signal receiving unit, for receiving disturbed signal, described disturbed signal comprises useful signal and interference signal;
Down-converter unit, obtains mixed frequency signal for the disturbed signal that received by described signal receiving unit and local oscillation signal after mixing and low-pass filtering treatment;
Filter unit, the mixed frequency signal for described down-converter unit being exported carries out Channel assignment filtering and obtains filtering signal;
Computing unit, for calculating the signal to noise ratio of described filtering signal;
Control unit, the signal to noise ratio for obtaining when described computing unit meets reception requirement, controls described signal receiving unit and continues to receive disturbed signal; The signal to noise ratio obtained when described computing unit does not meet reception requirement, controls described signal receiving unit and continue to receive disturbed signal after the frequency of adjustment local oscillation signal; Wherein, the local oscillation signal of described adjustment receiver is: be the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal and/or be centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal.
9. interference suppression equipment according to claim 8, is characterized in that, the initial value of the frequency of described local oscillation signal is set as centre frequency and the IF-FRE sum of useful signal.
10. interference suppression equipment according to claim 8, is characterized in that, the described signal to noise ratio that described computing unit obtains meets and receives the signal to noise ratio requiring to include described filtering signal and be greater than pre-determined threshold; The satisfied signal to noise ratio requiring to include described filtering signal that receives of the described signal to noise ratio that described computing unit obtains is less than described pre-determined threshold.
11. interference suppression equipments according to claim 10, is characterized in that, described pre-determined threshold is less than or equal to the demodulation threshold of baseband chip.
12. interference suppression equipments according to claim 10, is characterized in that, described control unit comprises:
First adjustment unit, for being less than described pre-determined threshold when described signal to noise ratio, and if the frequency of current local oscillation signal is centre frequency and the IF-FRE sum of useful signal, be the centre frequency of useful signal and the difference of IF-FRE by the frequency setting of local oscillation signal.
13. interference suppression equipments according to claim 12, is characterized in that, described control unit also comprises:
Second adjustment unit, for being less than described pre-determined threshold when described signal to noise ratio, and if the frequency of current local oscillation signal is the centre frequency of useful signal and the difference of IF-FRE, be centre frequency and the IF-FRE sum of useful signal by the frequency setting of local oscillation signal.
14. interference suppression equipments according to claim 8, is characterized in that, described computing unit comprises:
AD conversion unit, for being converted to digital signal by described filtering signal by analog signal;
Digital signal processing unit, for carrying out channel estimating to the filtering signal after described AD conversion unit conversion, and records the signal to noise ratio of described filtering signal.
15. 1 kinds of receivers, is characterized in that, comprise the interference suppression equipment according to any one of claim 9 to 14.
16. receivers according to claim 15, is characterized in that, also comprise local oscillator generating unit, and described local oscillator generating unit is connected to described down-converter unit and described control unit.
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| WO2015100725A1 (en) * | 2014-01-03 | 2015-07-09 | Telefonaktiebolaget L M Ericsson (Publ) | Method for adjusting lo frequencies in receiver and associated receiver |
| CN107479089B (en) * | 2017-09-08 | 2019-07-23 | 中国舰船研究设计中心 | A kind of power detector |
| CN108171118B (en) * | 2017-12-05 | 2020-10-02 | 东软集团股份有限公司 | Blink signal data processing method and device, readable storage medium and electronic equipment |
| CN108566203A (en) * | 2018-04-20 | 2018-09-21 | 中国地震局工程力学研究所 | A kind of collecting method and device |
| CN111313918B (en) * | 2018-12-29 | 2022-03-29 | 上海司南卫星导航技术股份有限公司 | Receiving device, terminal device and computer readable storage medium |
| CN109743066B (en) * | 2019-02-28 | 2020-12-15 | 重庆蓝岸通讯技术有限公司 | Terminal sensitivity reduction solution method based on camera master clock adjustment, storage medium and terminal |
| CN111901002B (en) * | 2019-05-05 | 2021-11-16 | 海能达通信股份有限公司 | Method for improving performance of low-intermediate frequency receiver, storage medium and receiver |
| CN113131952B (en) * | 2019-12-31 | 2022-10-14 | 海能达通信股份有限公司 | Blocking signal suppression method, signal demodulation method, device and related equipment |
| CN111510174B (en) * | 2020-04-21 | 2022-03-15 | 上海创远仪器技术股份有限公司 | Method for realizing image frequency suppression processing aiming at first-stage superheterodyne receiver |
| CN112822131A (en) * | 2020-12-31 | 2021-05-18 | 江苏创通电子股份有限公司 | Adjacent channel suppression circuit and adjacent channel suppression method |
| KR20230118674A (en) * | 2021-01-21 | 2023-08-11 | 하이테라 커뮤니케이션즈 코포레이션 리미티드 | Adaptive anti-interference method and adaptive anti-interference device |
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