CN103248304A - Tri-level inversion indirect vector control system based on simplified SVPWM (space vector pulse width modulation) - Google Patents

Tri-level inversion indirect vector control system based on simplified SVPWM (space vector pulse width modulation) Download PDF

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Publication number
CN103248304A
CN103248304A CN2013101424105A CN201310142410A CN103248304A CN 103248304 A CN103248304 A CN 103248304A CN 2013101424105 A CN2013101424105 A CN 2013101424105A CN 201310142410 A CN201310142410 A CN 201310142410A CN 103248304 A CN103248304 A CN 103248304A
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vector
voltage
svpwm
phase
inverter
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范波
赵伟刚
许惠
史光辉
谢冬冬
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Henan University of Science and Technology
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Henan University of Science and Technology
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Abstract

The invention relates to a tri-level inversion indirect vector control system based on simplified SVPWM (space vector pulse width modulation). On bases of the SVPWM simplification algorithm under a 60-degree coordinate system, an asynchronous motor dynamic mathematical model, a vector control fundamental principle and a main circuit in the step A, the tri-level inverter vector control system based on network parameter control (NPC) is established. The method dispenses with judgment that a reference voltage vector is in a large section or a small section, as well as a great deal of trigonometric functional operation, and only requires simple logical judgment, so that nearest three vectors for synthesizing the reference voltage vector can be obtained; and meanwhile, an output switch state equation is introduced in the algorithm, so that midpoint electric potential balance on the direct current side can be effectively controlled, and the method can be easily popularized to inverters with higher level.

Description

A kind of indirect vector control system of tri-level inversion based on simplifying SVPWM
Technical field
The invention belongs to high pressure, high power AC frequency control field, relate to a kind of indirect vector control system of diode-clamped (NPC) three-level inverter based on the SVPWM shortcut calculation.
Background technology
Since NPC tri-level topological structures propose, this structure is widely used in fields such as the transmission of mesohigh alternating current machine, electric network reactive compensation and generations of electricity by new energy.Than two level, the characteristics such as the NPC three-level inverter has the more approaching sine wave of output voltage, voltage change ratio is little, equivalent switching frequency is high, harmonic wave is little.But by each phase brachium pontis, can produce certain electric current due to its load current at the DC side mid point, make dividing potential drop capacitance voltage imbalance.The uneven meeting of capacitance voltage increases the harmonic content of output voltage waveforms, can strengthen the voltage stress of switching device simultaneously, even can damage switching device, puncture DC bus capacitor.Therefore, in frequency conversion speed-adjusting system, need to carry out by control algolithm the next balanced capacitance voltage of the degree of freedom of suitable selector switch state equation.
Summary of the invention
The present invention is for solving the problems of the technologies described above, a kind of indirect vector control system of tri-level inversion based on simplifying SVPWM has been proposed, this system has been saved judgement and a large amount of trigonometric function operation of large and small sector, reference voltage vector place, only need to carry out simple logic judgement, can obtain nearest three vectors for the synthesis of reference voltage vector; Simultaneously, introduced the output switch state equation in algorithm, can effectively control DC side midpoint potential balance, the method can be generalized to easily more and go in the high level inverter.
The present invention is that the technical scheme that the deficiency that solves the problems of the technologies described above adopts is: a kind of indirect vector control system of tri-level inversion based on simplifying SVPWM,
Step 1, foundation, based on NPC three-level inverter main circuit, are comprised of three-phase tri-level diode clamp formula inversion unit, rectification unit, filter unit, and each is comprised of inverter 4 IGBT switching tubes, 4 fly-wheel diodes, 2 clamping diodes; Whole three-phase inverter DC side is together in series and is supported and balanced DC voltage, wherein Cl=C2 by two capacitor C l, C2;
Step 2, utilize 60 ° of SVPWM shortcut calculations under coordinate system to make main circuit DC capacitor voltage balance in step 1;
The method of step 3, employing coordinate transform is simplified its Mathematical Modeling: when asynchronous motor is processed, ignore space harmonics, three phase windings are 120 ° of space mutual deviations, and the magnetomotive force produced distributes by sinusoidal rule along air gap periphery; Ignore magnetic circuit saturated, think that the self-induction of each winding and mutual inductance are all constant; Ignore core loss; Do not consider the impact on winding resistance of frequency change and variations in temperature;
Step 4, according to the asynchronous motor dynamic mathematical models in step 3 and the basic principle of vector control, the main circuit of take in step 1 is basis, sets up the indirect vector control system based on the NPC three-level inverter.
Described step 1 is that inverter is every to be comprised of 4 IGBT switching tubes, 4 fly-wheel diodes, 2 clamping diodes; Whole three-phase inverter DC side is together in series and is supported and balanced DC voltage by two capacitor C l, C2, wherein Cl=C2, control by certain switching logic, and AC produces the phase voltage of three kinds of voltages, at the output synthesis sine, the dynamic mathematical models of its main circuit are: , wherein
Figure RE-DEST_PATH_IMAGE004
,
Figure RE-DEST_PATH_IMAGE006
,
Figure RE-DEST_PATH_IMAGE008
be respectively A, B, C three-phase phase current, R, L are respectively resistance value, the inductance value of AC,
Figure RE-DEST_PATH_IMAGE010
for DC voltage,
Figure RE-DEST_PATH_IMAGE012
,
Figure RE-DEST_PATH_IMAGE014
,
Figure RE-DEST_PATH_IMAGE016
,
Figure RE-DEST_PATH_IMAGE018
for the switch function of inverter A, B, C three-phase,
Figure RE-DEST_PATH_IMAGE020
,
Figure RE-DEST_PATH_IMAGE022
,
Figure RE-DEST_PATH_IMAGE024
be respectively AC A, B, C three-phase voltage source.
The SVPWM shortcut calculation based under 60 ° of coordinate systems of described step 2 is,
Step 1, coordinate transform: NPC three-level inverter fundamental space regular hexagon polar plot is adopted to non-orthogonal 60 ° of coordinate systems,
Figure RE-DEST_PATH_IMAGE026
coordinate system replaces traditional orthogonal coordinate system, by the Clark conversion, and by the length of small vector is
Figure RE-DEST_PATH_IMAGE028
regulation, by the normalization of fundamental space polar plot;
Determining of step 2, basic vector: after normalized, by the coordinate figure normalizing of all space vectors, it is integer, the method that adopts the space vector of voltage coordinate figure to round up and down, and nearest three vector principles are determined the fundamental space vector of synthesized reference space vector
Figure RE-DEST_PATH_IMAGE030
,
Figure RE-DEST_PATH_IMAGE032
,
Figure RE-DEST_PATH_IMAGE034
;
The calculating of step 3, vector action time: for a given reference voltage space vector
Figure RE-DEST_PATH_IMAGE036
, by the weber equilibrium principle
Figure RE-DEST_PATH_IMAGE038
,
Figure RE-DEST_PATH_IMAGE040
for PWM interrupt cycle, calculate the action time of each basic vector of being determined by step 3
Figure RE-DEST_PATH_IMAGE042
,
Figure RE-DEST_PATH_IMAGE044
, ;
Determining of step 4, output switch state: getting nearest three vectors is:
Figure RE-DEST_PATH_IMAGE048
, the on off state that this basic vector is corresponding is: , switching vector selector can be designated as: , according to the impact of large vector, middle vector, positive small vector, negative small vector alignment voltage, select different
Figure RE-DEST_PATH_IMAGE054
, just can select different redundancy vectors, obtain three nearest basic vectors
Figure RE-DEST_PATH_IMAGE056
corresponding whole on off state, obtain different on off sequence pulses, by the conducting to the three-level inverter switching tube and shutoff, controlled, and controls neutral point voltage balance.
Described step 4 is, according to the fundamental equation of vector control, sets up based on the slip frequency Vector Speed-Control System, and the system main circuit has adopted SVPWM voltage-type three-level inverter, and rotating speed is taked slip frequency controlled, i.e. the asynchronous motor stator angular frequency
Figure RE-DEST_PATH_IMAGE058
by the rotor angle frequency
Figure RE-DEST_PATH_IMAGE060
and slip angular frequency form (
Figure RE-DEST_PATH_IMAGE064
); Its vector control equation is as follows:
Figure RE-DEST_PATH_IMAGE066
,
Figure RE-DEST_PATH_IMAGE068
,
Figure RE-DEST_PATH_IMAGE070
, in formula
Figure RE-DEST_PATH_IMAGE072
for electromagnetic torque,
Figure RE-DEST_PATH_IMAGE074
for the magnetic pole logarithm of asynchronous machine,
Figure RE-DEST_PATH_IMAGE076
for the rotor mutual inductance,
Figure RE-DEST_PATH_IMAGE078
for rotor winding self-induction,
Figure RE-DEST_PATH_IMAGE080
,
Figure RE-DEST_PATH_IMAGE082
be respectively excitation component and the torque component of stator current,
Figure RE-DEST_PATH_IMAGE084
for rotor flux,
Figure RE-DEST_PATH_IMAGE086
for rotor time constant,
Figure RE-DEST_PATH_IMAGE088
for differential operator, native system adopts the constant control of magnetic flux,
Figure RE-DEST_PATH_IMAGE090
; Obtained excitation component and the torque component of stator current by the vector control equation, system is converted to voltage control by Current Control accordingly, and its transformation relation is:
Figure RE-DEST_PATH_IMAGE092
, in formula
Figure RE-DEST_PATH_IMAGE094
,
Figure RE-DEST_PATH_IMAGE096
for excitation component and the torque component of stator voltage,
Figure RE-DEST_PATH_IMAGE098
for magnetic leakage factor ( ),
Figure 177705DEST_PATH_IMAGE094
,
Figure 566703DEST_PATH_IMAGE096
through the conversion of two-phase rotating coordinate system/three phase static coordinate system, obtain the voltage control signal of SVPWM inverter, and the output voltage of control inverter, thereby make asynchronous motor drag load running.
The invention beneficial effect is: in traditional SVPWM algorithm, the judgement of reference voltage space vector sector and calculating basic vector aspect action time, relate to more trigonometric function operation and table lookup, for utilizing embedded system to realize these operations, can take a plurality of cpu clock cycles, be not easy to the real-time control to load.The existing algorithm that improves has: three level SVPWMs are decomposed into to two level SVPWMs; Orthogonal coordinate system is converted under KL coordinate system and 60 ° of coordinate systems.Although algorithm has been simplified in above improvement, do not consider the fluctuation of electric capacity mid-point voltage.Adopt this method, characteristics according to polar plot, adopt nonopiate 60 ° of coordinate systems to replace traditional orthogonal coordinate system, by coordinate transform, make phasor coordinate be normalized to integer, the reference vector coordinate is made progress respectively, rounds downwards and determine basic vector, and utilize the weber equilibrium principle to calculate its action time; The insertion switch state equation, choose appropriate freedom according to the impact of different vector alignment voltages
Figure 676611DEST_PATH_IMAGE054
, realize the control of alignment voltage.This method, without reference vector is carried out to the sector judgement, is avoided complicated triangulo operation, than traditional algorithm, has saved amount of calculation, has realized the real-time control to three-level inverter, and reduces the rotation pulsation of motor.
The accompanying drawing explanation
The topological structure that accompanying drawing 1 is Diode-clamped Three-level Inverter.
Accompanying drawing 2 is indirect vector control system schematic diagram.
The simplified model that accompanying drawing 3 is three-level inverter.
The polar plot of the NPC three-level inverter that accompanying drawing 4 is the SVPWM algorithm based on 60 ° of coordinate systems.
Accompanying drawing 5 is that little delta-shaped region is divided figure.
The drift condition that accompanying drawing 6 is mid-point voltage while adopting traditional algorithm.
The drift condition of mid-point voltage when accompanying drawing 7 is the SVPWM algorithm adopted based on 60 ° of coordinate systems.
Embodiment
A kind of indirect vector control system of tri-level inversion based on simplifying SVPWM comprises following step:
The first step, set up the main circuit of NPC three-level inverter, and each needs 4 IGBT switching tubes, 4 fly-wheel diodes, 2 clamping diodes mutually inverter; Whole three-phase inverter DC side is together in series and is supported and balanced DC voltage by two capacitor C l, C2, Cl=C2.By certain switching logic, control, AC produces the phase voltage of three kinds of voltages, at the output synthesis sine.The Mathematical Modeling of three-level inverter is to make , , switch function for inverter A, B, C three-phase, have,
Figure RE-DEST_PATH_IMAGE102
, inverter output phase voltage is expressed as with switch function
Figure RE-DEST_PATH_IMAGE104
, whole three-level inverter three-phase has 3 * 3 * 3=27 group output state, by three-level inverter main circuit simplified model as shown in Figure 3, can obtain the differential equation of three-phase circuit:
Figure RE-DEST_PATH_IMAGE106
, arrangement can obtain the Mathematical Modeling of three-level inverter main circuit:
Figure 638696DEST_PATH_IMAGE002
, wherein
Figure 181672DEST_PATH_IMAGE004
,
Figure 601677DEST_PATH_IMAGE006
, be respectively A, B, C three-phase phase current, R, L are respectively resistance value, the inductance value of AC,
Figure 340012DEST_PATH_IMAGE010
for DC voltage,
Figure 116207DEST_PATH_IMAGE012
,
Figure 223840DEST_PATH_IMAGE014
, ,
Figure 420040DEST_PATH_IMAGE018
for the switch function of inverter A, B, C three-phase,
Figure 570398DEST_PATH_IMAGE020
,
Figure 962065DEST_PATH_IMAGE022
,
Figure 223282DEST_PATH_IMAGE024
be respectively AC A, B, C three-phase voltage source.
Second step, for solving main circuit DC capacitor voltage imbalance problem, propose a kind of SVPWM shortcut calculation based under 60 ° of coordinate systems, and embodiment is as follows:
A) consider that NPC three-level inverter fundamental space polar plot is regular hexagon, adopt non-orthogonal 60 .coordinate system (
Figure 742427DEST_PATH_IMAGE026
coordinate system) replace traditional orthogonal coordinate system, establish reference voltage vector and be
Figure RE-DEST_PATH_IMAGE108
? coordinate in coordinate system be (
Figure RE-DEST_PATH_IMAGE112
, ),
Figure 502834DEST_PATH_IMAGE026
coordinate under coordinate system be ( ,
Figure RE-DEST_PATH_IMAGE118
),
Figure RE-DEST_PATH_IMAGE120
coordinate in coordinate system is
Figure RE-DEST_PATH_IMAGE122
, by Clark, converted
Figure RE-DEST_PATH_IMAGE124
, and by the length of small vector be regulation, by after the normalization of fundamental space polar plot, the basic vector of three-level inverter is transformed to
Figure 945579DEST_PATH_IMAGE026
coordinate system, the three dimensional vector diagram that transforms to three-level inverter under 60 ° of coordinate systems obtained, as shown in Figure 4.
Therefore b) after normalized, under 60 ° of coordinates, the coordinate figure of all space basic vectors is integer, for georeferencing voltage vector arbitrarily
Figure 807225DEST_PATH_IMAGE108
, choosing of basic vector can adopt the method rounded up and down by its coordinate, and according to nearest three vector principles, just can determine basic vector to be
Figure RE-DEST_PATH_IMAGE128
,
Figure 520491DEST_PATH_IMAGE032
, .
C) after obtaining nearest three vectors according to said method, for a given reference space voltage vector
Figure 175649DEST_PATH_IMAGE036
, by the weber equilibrium principle,
Figure RE-DEST_PATH_IMAGE130
, can be under 60 ° of coordinate systems action time of each basic vector
Figure 917951DEST_PATH_IMAGE042
,
Figure 623738DEST_PATH_IMAGE044
,
Figure 83539DEST_PATH_IMAGE046
.Without carrying out complicated trigonometric function operation, only contain simple arithmetical operation based on 60 ° of coordinate systems, can simplify a large amount of computings, for NPC three-level inverter SVPWM is provided by a kind of highly effective method that provides in real time.
D) in order further to determine the output switch state of inverter three-phase brachium pontis, to establish nearest three vectors, be:
, wherein ,
Figure RE-DEST_PATH_IMAGE134
; If the on off state that this basic vector is corresponding is:
Figure RE-DEST_PATH_IMAGE136
, wherein
Figure RE-DEST_PATH_IMAGE138
, switching vector selector can be designated as:
Figure RE-DEST_PATH_IMAGE140
, wherein , in the situation that meet above-mentioned condition, different by selecting
Figure 205231DEST_PATH_IMAGE054
just can obtain three nearest basic vectors corresponding whole on off state.
For example, hypothetical reference voltage vector
Figure RE-DEST_PATH_IMAGE144
, known this reference vector is positioned at the A3 community of the large sector of A, and as shown in Figure 5, its nearest three space vectors in 60 ° of coordinate systems are respectively
Figure RE-DEST_PATH_IMAGE146
,
Figure RE-DEST_PATH_IMAGE148
,
Figure RE-DEST_PATH_IMAGE150
, can obtain its on off state according to the switching vector selector equation in step d) and be respectively 100 or 0-1-1,10-1,110 or 00-1, according to weber equilibrium principle be respectively action time that can obtain each vector
Figure RE-DEST_PATH_IMAGE152
,
Figure RE-DEST_PATH_IMAGE154
,
Figure RE-DEST_PATH_IMAGE156
.Just decided the action time of the assembled state of the switching tube of each vector representative (IGBT), according to these, just can produce a series of pwm pulse sequences conducting and the shutoff of three-level inverter switching tube are controlled.
According to the on off state equation, select different
Figure 586665DEST_PATH_IMAGE054
, just can select different redundancy vectors, obtain different on off sequence pulses.As above in example
Figure 918727DEST_PATH_IMAGE146
, when
Figure RE-DEST_PATH_IMAGE158
the time obtain negative small vector 0-1-1(onn), when
Figure RE-DEST_PATH_IMAGE160
the time obtain positive small vector 100(poo), yet the effect of positive and negative small vector alignment current potential is just the opposite, therefore, as long as suitably select the degree of freedom according to the non-equilibrium state of DC side midpoint potential , just can obtain the effective control to Diode-clamped Three-level Inverter midpoint potential balance.
When adopting the SVPWM algorithm based under 60 ° of coordinate systems of the present invention and adopting traditional algorithm, accompanying drawing 6 and accompanying drawing 7 are shown in the deviation ratio of mid-point voltage.
The 3rd step, the Mathematical Modeling of simplification asynchronous motor.Take and produce same rotating mmf as criterion, three-phase alternating current winding, two cross streams windings and integrally rotated direct current winding be equivalence each other.In other words, under three phase coordinate systems
Figure RE-DEST_PATH_IMAGE162
with
Figure RE-DEST_PATH_IMAGE164
with the direct current under rotation two phase coordinate systems
Figure RE-DEST_PATH_IMAGE166
with be equivalent, they can produce identical rotating mmf.Just
Figure RE-DEST_PATH_IMAGE170
,
Figure RE-DEST_PATH_IMAGE172
two windings, look when the observer stands in ground, and they are the rotation direct current windings with the equivalence of three-phase alternating current winding; If jump on the iron core rotated, see, their DC motor models really just.Like this, by the conversion of coordinate system, can find the DC motor model with the equivalence of AC three-phase winding.
Three-phase closes to the current transformation between the two-phase rest frame:
Figure RE-DEST_PATH_IMAGE174
, in formula,
Figure RE-DEST_PATH_IMAGE176
for the current transformation battle array of three-phase coordinate system transformation to two phase coordinate systems, produce identical magnetomotive principle and the constant principle of conversion front and back power according to them, can obtain:
Figure RE-DEST_PATH_IMAGE178
, the transformation matrix that the two-phase static coordinate is tied to the two-phase rotating coordinate system is
Figure RE-DEST_PATH_IMAGE180
, simplify the Mathematical Modeling of asynchronous motor by coordinate transform.
The 4th step, the present invention's Vector Speed-Control System used mainly is comprised of main circuit and control circuit two parts.Main circuit has adopted the SVPWM voltage source inverter.Rotating speed adopts slip frequency controlled, i.e. asynchronous motor stator angular frequency
Figure 592865DEST_PATH_IMAGE058
by the rotor angle frequency
Figure RE-DEST_PATH_IMAGE182
and slip angular frequency form (
Figure RE-DEST_PATH_IMAGE186
).Like this, in the rotation speed change process, the stator current frequency of motor can synchronously change with the actual speed of rotor all the time, makes the adjusting of rotating speed more level and smooth.
The fundamental equation of vector control system is
Figure 912244DEST_PATH_IMAGE066
,
Figure 474812DEST_PATH_IMAGE068
,
Figure 972395DEST_PATH_IMAGE070
, in formula
Figure 569598DEST_PATH_IMAGE072
for electromagnetic torque,
Figure 542102DEST_PATH_IMAGE074
for the magnetic pole logarithm of asynchronous machine,
Figure 529650DEST_PATH_IMAGE076
for the rotor mutual inductance,
Figure 878592DEST_PATH_IMAGE078
for rotor winding self-induction,
Figure 270914DEST_PATH_IMAGE080
,
Figure 679899DEST_PATH_IMAGE082
be respectively excitation component and the torque component of stator current, for rotor flux,
Figure 41796DEST_PATH_IMAGE086
for rotor time constant,
Figure 348012DEST_PATH_IMAGE088
for differential operator.
The basic exercise equation that all will obey in electric drive control system is:
Figure RE-DEST_PATH_IMAGE188
, the dynamic property of governing system is provided, be mainly to rely on the rate of change improved rotating speed
Figure RE-DEST_PATH_IMAGE190
control.Obviously, by controlling
Figure 117779DEST_PATH_IMAGE072
just can reach control
Figure 79918DEST_PATH_IMAGE190
purpose.Slip frequency vector control is exactly by controlling slip angular frequency
Figure 770663DEST_PATH_IMAGE184
control
Figure 934315DEST_PATH_IMAGE072
thereby, indirectly control rotating speed.
Keeping under the control that rotor flux is constant, motor torque directly is subject to the torque component of stator current
Figure 622786DEST_PATH_IMAGE082
control, and slip angular frequency
Figure 134538DEST_PATH_IMAGE184
can be by the torque component of stator current
Figure 301078DEST_PATH_IMAGE082
calculate rotor flux
Figure 581886DEST_PATH_IMAGE084
also can calculate by the excitation component of stator current.In system, rotating speed is regulated by speed regulator PI, the torque component of output stator electric current
Figure 494786DEST_PATH_IMAGE082
, then calculate torque
Figure 165938DEST_PATH_IMAGE072
.Because the present invention adopts the control that magnetic flux is constant, .
What obtain due to the vector control equation is excitation component and the torque component of stator current, and the present invention has adopted voltage source inverter, needs accordingly Current Control is converted to voltage control, and its transformation relation is:
Figure 537063DEST_PATH_IMAGE092
, in formula
Figure 629653DEST_PATH_IMAGE094
, for excitation component and the torque component of stator voltage, for magnetic leakage factor (
Figure 617091DEST_PATH_IMAGE100
). ,
Figure 526327DEST_PATH_IMAGE096
through the conversion of two-phase rotating coordinate system/three phase static coordinate system, obtain the voltage control signal of SVPWM inverter, and the output voltage of control inverter, thereby make asynchronous motor drag load running.
  

Claims (4)

1. the indirect vector control system of tri-level inversion based on simplifying SVPWM is characterized in that:
Step 1, foundation, based on NPC three-level inverter main circuit, are comprised of three-phase tri-level diode clamp formula inversion unit, rectification unit, filter unit, and each is comprised of inverter 4 IGBT switching tubes, 4 fly-wheel diodes, 2 clamping diodes; Whole three-phase inverter DC side is together in series and is supported and balanced DC voltage, wherein Cl=C2 by two capacitor C l, C2;
Step 2, utilize 60 ° of SVPWM shortcut calculations under coordinate system to make main circuit DC capacitor voltage balance in step 1;
The method of step 3, employing coordinate transform is simplified its Mathematical Modeling: when asynchronous motor is processed, ignore space harmonics, three phase windings are 120 ° of space mutual deviations, and the magnetomotive force produced distributes by sinusoidal rule along air gap periphery; Ignore magnetic circuit saturated, think that the self-induction of each winding and mutual inductance are all constant; Ignore core loss; Do not consider the impact on winding resistance of frequency change and variations in temperature;
Step 4, according to the asynchronous motor dynamic mathematical models in step 3 and the basic principle of vector control, the main circuit of take in step 1 is basis, sets up the indirect vector control system based on the NPC three-level inverter.
2. a kind of indirect vector control system of tri-level inversion based on simplifying SVPWM as claimed in claim 1, it is characterized in that: described step 1 is that inverter is every to be comprised of 4 IGBT switching tubes, 4 fly-wheel diodes, 2 clamping diodes; Whole three-phase inverter DC side is together in series and is supported and balanced DC voltage by two capacitor C l, C2, wherein Cl=C2, control by certain switching logic, and AC produces the phase voltage of three kinds of voltages, at the output synthesis sine, the dynamic mathematical models of its main circuit are:
Figure 297277DEST_PATH_IMAGE002
, wherein
Figure 820050DEST_PATH_IMAGE004
,
Figure 696739DEST_PATH_IMAGE006
,
Figure 643835DEST_PATH_IMAGE008
be respectively A, B, C three-phase phase current, R, L are respectively resistance value, the inductance value of AC,
Figure 35502DEST_PATH_IMAGE010
for DC voltage,
Figure 296719DEST_PATH_IMAGE012
,
Figure 93161DEST_PATH_IMAGE014
,
Figure 211159DEST_PATH_IMAGE016
,
Figure 27805DEST_PATH_IMAGE018
for the switch function of inverter A, B, C three-phase,
Figure 889451DEST_PATH_IMAGE020
,
Figure 537470DEST_PATH_IMAGE022
,
Figure 32561DEST_PATH_IMAGE024
be respectively AC A, B, C three-phase voltage source.
3. as one kind of the claim 1 indirect vector control system of tri-level inversion based on simplifying SVPWM, it is characterized in that: the SVPWM shortcut calculation based under 60 ° of coordinate systems of described step 2 is,
Step 1, coordinate transform: NPC three-level inverter fundamental space regular hexagon polar plot is adopted to non-orthogonal 60 ° of coordinate systems,
Figure 398820DEST_PATH_IMAGE026
coordinate system replaces traditional orthogonal coordinate system, by the Clark conversion, and by the length of small vector is regulation, by the normalization of fundamental space polar plot;
Determining of step 2, basic vector: after normalized, by the coordinate figure normalizing of all space vectors, it is integer, the method that adopts the space vector of voltage coordinate figure to round up and down, and nearest three vector principles are determined the fundamental space vector of synthesized reference space vector
Figure 504365DEST_PATH_IMAGE030
,
Figure 964165DEST_PATH_IMAGE032
,
Figure 832369DEST_PATH_IMAGE034
;
The calculating of step 3, vector action time: for a given reference voltage space vector
Figure 973500DEST_PATH_IMAGE036
, by the weber equilibrium principle
Figure 596112DEST_PATH_IMAGE038
, for PWM interrupt cycle, calculate the action time of each basic vector of being determined by step 3
Figure 505348DEST_PATH_IMAGE042
, ,
Figure 992534DEST_PATH_IMAGE046
;
Determining of step 4, output switch state: getting nearest three vectors is: , the on off state that this basic vector is corresponding is:
Figure 559968DEST_PATH_IMAGE050
, switching vector selector can be designated as: , according to the impact of large vector, middle vector, positive small vector, negative small vector alignment voltage, select different
Figure 643035DEST_PATH_IMAGE054
, just can select different redundancy vectors, obtain three nearest basic vectors
Figure 881118DEST_PATH_IMAGE056
corresponding whole on off state, obtain different on off sequence pulses, by the conducting to the three-level inverter switching tube and shutoff, controlled, and controls neutral point voltage balance.
4. as claim 1 indirect vector control system of tri-level inversion based on simplifying SVPWM, it is characterized in that: described step 4 is, fundamental equation according to vector control, foundation is based on the slip frequency Vector Speed-Control System, the system main circuit has adopted SVPWM voltage-type three-level inverter, rotating speed is taked slip frequency controlled, i.e. the asynchronous motor stator angular frequency
Figure 930983DEST_PATH_IMAGE058
by the rotor angle frequency
Figure 217607DEST_PATH_IMAGE060
and slip angular frequency
Figure 406668DEST_PATH_IMAGE062
form ( ); Its vector control equation is as follows:
Figure 290496DEST_PATH_IMAGE066
,
Figure 443129DEST_PATH_IMAGE068
,
Figure 749345DEST_PATH_IMAGE070
, in formula
Figure 992546DEST_PATH_IMAGE072
for electromagnetic torque,
Figure 17003DEST_PATH_IMAGE074
for the magnetic pole logarithm of asynchronous machine,
Figure 707747DEST_PATH_IMAGE076
for the rotor mutual inductance,
Figure 71732DEST_PATH_IMAGE078
for rotor winding self-induction,
Figure 556940DEST_PATH_IMAGE080
, be respectively excitation component and the torque component of stator current,
Figure 503741DEST_PATH_IMAGE084
for rotor flux,
Figure 518970DEST_PATH_IMAGE086
for rotor time constant, for differential operator, native system adopts the constant control of magnetic flux,
Figure 111812DEST_PATH_IMAGE090
; Obtained excitation component and the torque component of stator current by the vector control equation, system is converted to voltage control by Current Control accordingly, and its transformation relation is:
Figure 412868DEST_PATH_IMAGE092
, in formula
Figure 548183DEST_PATH_IMAGE094
, for excitation component and the torque component of stator voltage,
Figure 799221DEST_PATH_IMAGE098
for magnetic leakage factor (
Figure 638389DEST_PATH_IMAGE100
),
Figure 628210DEST_PATH_IMAGE094
,
Figure 829385DEST_PATH_IMAGE096
through the conversion of two-phase rotating coordinate system/three phase static coordinate system, obtain the voltage control signal of SVPWM inverter, and the output voltage of control inverter, thereby make asynchronous motor drag load running.
CN2013101424105A 2013-04-23 2013-04-23 Tri-level inversion indirect vector control system based on simplified SVPWM (space vector pulse width modulation) Pending CN103248304A (en)

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CN103633862A (en) * 2013-10-08 2014-03-12 江苏有能新能源有限公司 SVPWM frequency conversion device reducing intermediate operation and modulation method thereof
CN103684013A (en) * 2013-12-17 2014-03-26 中国矿业大学 SVPWM control method of fast multilevel inverter
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CN104270060A (en) * 2014-10-13 2015-01-07 淮阴师范学院 Coordinate component SVPWM control method for variable frequency speed regulation of three-phase asynchronous motor
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CN104753381A (en) * 2015-03-26 2015-07-01 西南交通大学 45 degree SVPWM (space vector pulse width modulation) modulation algorithm of three phase and three level NPC convertor
CN104796026A (en) * 2015-05-12 2015-07-22 中国矿业大学 Multi-object control method of three-level frequency converter
CN105356765A (en) * 2015-12-09 2016-02-24 哈尔滨理工大学 Control system and control method of indirect space vector matrix converter based on 60-degree coordinate system
CN105763126A (en) * 2016-04-29 2016-07-13 洛阳理工学院 Induction motor feedback type indirect vector control system and control method thereof
CN105811842A (en) * 2016-04-29 2016-07-27 洛阳理工学院 Feedforward type indirection vector control system and control method for induction motor
CN106130388A (en) * 2016-07-22 2016-11-16 东北大学秦皇岛分校 Inverter space vector control method and device
CN107391923A (en) * 2017-07-18 2017-11-24 华南理工大学 Based on the three-level inverter error current analysis method for simplifying SVPWM strategies
CN107425770A (en) * 2017-08-17 2017-12-01 贵州电网有限责任公司贵阳供电局 AC variable-frequency speed regulation system and speed regulating method based on ARM microprocessor
CN107526858A (en) * 2016-11-07 2017-12-29 北京交通大学 Ferroelectric tractive power supply system emulation platform based on PSCAD/EMTDC
CN108974055A (en) * 2018-08-06 2018-12-11 江西理工大学 The multi-modal optimization drive control method of suspension type maglev train system
CN109831136A (en) * 2019-04-12 2019-05-31 广东工业大学 A kind of driving method of three phase alternating current motor, system and device
CN111865125A (en) * 2020-07-29 2020-10-30 中车青岛四方车辆研究所有限公司 Traction inverter control system and PWM modulation method
CN112087157A (en) * 2020-08-28 2020-12-15 南京南瑞继保电气有限公司 Modulation method of three-level converter and three-level converter
WO2024067836A1 (en) * 2022-09-30 2024-04-04 上海正泰电源系统有限公司 Voltage regulation method for three-phase four-bridge-arm three-level inverter

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CN103560691B (en) * 2013-11-11 2015-11-25 西华大学 A kind of method of non-angular computing SVPWM and grid-connected inverting system
CN103560691A (en) * 2013-11-11 2014-02-05 西华大学 Non-angle operation SVPWM method and grid-connected inverter system
CN103684013A (en) * 2013-12-17 2014-03-26 中国矿业大学 SVPWM control method of fast multilevel inverter
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CN103916037B (en) * 2014-04-15 2016-06-01 中国矿业大学 Based on the three-level current transformer space vector modulating method of gh system of coordinates
CN103916037A (en) * 2014-04-15 2014-07-09 中国矿业大学 Three-level current transformer space vector modulation scheme based on gh coordinate system
CN104270060A (en) * 2014-10-13 2015-01-07 淮阴师范学院 Coordinate component SVPWM control method for variable frequency speed regulation of three-phase asynchronous motor
CN104506064A (en) * 2014-12-03 2015-04-08 许继电气股份有限公司 Space vector modulation method of three-level current converter
CN104617804A (en) * 2015-01-19 2015-05-13 云南电网有限责任公司电力科学研究院 Space vector pulse width modulation method
CN104753381A (en) * 2015-03-26 2015-07-01 西南交通大学 45 degree SVPWM (space vector pulse width modulation) modulation algorithm of three phase and three level NPC convertor
CN104796026A (en) * 2015-05-12 2015-07-22 中国矿业大学 Multi-object control method of three-level frequency converter
CN105356765A (en) * 2015-12-09 2016-02-24 哈尔滨理工大学 Control system and control method of indirect space vector matrix converter based on 60-degree coordinate system
CN105356765B (en) * 2015-12-09 2018-02-27 哈尔滨理工大学 A kind of control system and control method of the indirect space vector matrix converter based on 60 ° of coordinate systems
CN105763126A (en) * 2016-04-29 2016-07-13 洛阳理工学院 Induction motor feedback type indirect vector control system and control method thereof
CN105811842A (en) * 2016-04-29 2016-07-27 洛阳理工学院 Feedforward type indirection vector control system and control method for induction motor
CN105763126B (en) * 2016-04-29 2018-06-22 洛阳理工学院 A kind of indirect vector control system of induction conductivity feedback-type and its control method
CN105811842B (en) * 2016-04-29 2018-05-04 洛阳理工学院 A kind of indirect vector control system of induction conductivity feed-forward type and its control method
CN106130388B (en) * 2016-07-22 2019-06-18 东北大学秦皇岛分校 Inverter space vector control method and device
CN106130388A (en) * 2016-07-22 2016-11-16 东北大学秦皇岛分校 Inverter space vector control method and device
CN107526858B (en) * 2016-11-07 2023-12-22 北京交通大学 PSCAD/EMTDC-based simulation platform for electric iron traction power supply system
CN107526858A (en) * 2016-11-07 2017-12-29 北京交通大学 Ferroelectric tractive power supply system emulation platform based on PSCAD/EMTDC
CN107391923A (en) * 2017-07-18 2017-11-24 华南理工大学 Based on the three-level inverter error current analysis method for simplifying SVPWM strategies
CN107425770A (en) * 2017-08-17 2017-12-01 贵州电网有限责任公司贵阳供电局 AC variable-frequency speed regulation system and speed regulating method based on ARM microprocessor
CN108974055B (en) * 2018-08-06 2020-08-07 江西理工大学 Multi-mode optimized driving control method for suspension type magnetic suspension train system
CN108974055A (en) * 2018-08-06 2018-12-11 江西理工大学 The multi-modal optimization drive control method of suspension type maglev train system
CN109831136A (en) * 2019-04-12 2019-05-31 广东工业大学 A kind of driving method of three phase alternating current motor, system and device
CN109831136B (en) * 2019-04-12 2021-03-16 广东工业大学 Method, system and device for driving three-phase alternating current motor
CN111865125A (en) * 2020-07-29 2020-10-30 中车青岛四方车辆研究所有限公司 Traction inverter control system and PWM modulation method
CN111865125B (en) * 2020-07-29 2021-07-20 中车青岛四方车辆研究所有限公司 Traction inverter control system and PWM modulation method
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