CN103237001B - Advanced Metering Infrastructure (AMI) system carrier communication module self-adaptive modulation and coding method - Google Patents
Advanced Metering Infrastructure (AMI) system carrier communication module self-adaptive modulation and coding method Download PDFInfo
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Abstract
The invention discloses an advanced metering infrastructure (AMI) system carrier communication module self-adaptive modulation and coding method. The method comprises the following steps of inputting a code stream through a forward error correction coder to a serial-parallel converter; converting the serial data to a parallel code stream through the serial-parallel converter; setting a comparison threshold, and carrying out the threshold comparison between a subcarrier channel estimation value and a threshold comparative value; determining a subchannel modulation mode through a subchannel according to a comparison result; and modulating the subchannel according to the determined subchannel modulation mode. The modulation way of each subchannel is adaptively adjusted according to the signal-to-noise ratio, and corresponding demodulation is carried out on a receiving end; a modulation way with strong robustness is used for the subchannel with severe noise interference so as to improve the interference resistance; a modulation and coding way is determined according to the signal-to-noise ratio of the subchannel, higher transmission power is allocated to the subchannel with a high signal-to-noise ratio, and a modulation way with a high transmission rate is adopted; and the transmission efficiency and the interference resistance of the entire system can be improved.
Description
Technical field
The present invention relates to modulation and coding method, particularly a kind of AMI system carrier communication module adaptive modulation and coding method.
Background technology
Existing Automatic meter reading system multi-carrier communication module, the standard of realization has G3 standard OFDM power-line carrier communication and PRIME standard OFDM power-line carrier communication.PRIME standard physical layer and G3 standard class seemingly, so illustrate the shortcoming of prior art here as an example of G3 standard example.The physical layer of G3 standard adopts in transmitting terminal baseband modulation mode the modulation system that all subcarriers are identical, and for the serious subchannel of noise jamming, its error rate is high, and efficiency of transmission is low.Also without judgement, adopt the demodulation mode that all subcarriers are identical at receiving terminal.Although algorithm operating is simple like this, do not need the pre-estimation of receiving terminal channel conditions, for the serious subchannel of channel disturbance, its information will heavy damage, or efficiency of transmission is extremely low, and major defect is as follows:
1. its robustness of subcarrier that noise jamming is larger will die down, so error of transmission is more serious, efficiency of transmission is low.
2. for the higher subcarrier of signal to noise ratio, adopt the modulation system of low transmission efficiency by waste bandwidth.
3. all subcarriers adopt identical modulation and demodulation mode, will reduce efficiency of transmission and the antijamming capability of whole system.
Summary of the invention
The object of this invention is to provide a kind of AMI system carrier communication module adaptive modulation and coding method of efficient and high anti-jamming capacity.
This AMI system carrier communication module adaptive modulation and coding method provided by the invention, the method comprises the steps:
Step 1, input code flow, through forward error correction coder, inputs to serial-parallel converter;
Step 2, serial data is converted to parallel code stream by serial-parallel converter;
Step 3, sets up comparison threshold, and sub-carrier channels valuation and this comparison threshold are compared;
Step 4, subchannel is determined sub-channel modulation pattern according to the comparative result of step 3;
Step 5, carries out sub-channel modulation according to definite sub-channel modulation pattern.
Described sub-carrier channels valuation is for obtaining the signal to noise ratio of subchannel.
Comprise-5dB of described comparison threshold, 0dB, 5dB; In the time of be less than-5dB of subchannel signal to noise ratio, determine the modulating mode with ROBO; As be more than or equal to-5dB of subchannel signal to noise ratio and while being less than 0dB, determine the modulation system with DBPSK; In the time that subchannel signal to noise ratio is more than or equal to 0dB and is less than 5dB, determine the modulation system with DQPSK; In the time that subchannel signal to noise ratio is more than or equal to 5dB, determine the modulation system with D8PSK.
Constellation point under described DBPSK pattern distributes, and input bit pattern (X) is mapped as a symbol in constellation point, and its mapping mode is by existing mapped mode planisphere difference two-phase phase shift, the mapped mode planisphere after being improved; The variation of its output phase is as follows,
When input code flow is 1, its output phase
θ k=
φ k, output symbol is+1,
When input code flow is-1, its output phase
θ k=
φ k+ π, output symbol is-1;
Input bit pattern (X) is carried out to mapping code, input 0 and be expressed as-1, input 1 be expressed as+1, the modulation formula of inputting bit pattern (X) is: S=cos
θ k+ j × sin
θ k=X.
Constellation point under described DQPSK pattern distributes, and input bit pattern (X, Y) is mapped as a symbol in constellation point, and its mapping mode is by existing mapped mode planisphere difference four phase phase shifts, the mapped mode planisphere after being improved; The variation of its output phase is as follows,
When input code flow is 00, its output phase
θ k=
φ k+ π/4, output symbol is
,
When input code flow is 01, its output phase
θ k=
φ k+ 7 π/4, output symbol is
,
When input code flow is 11, its output phase
θ k=
φ k+ 5 π/4, output symbol is
,
When input code flow is 10, its output phase
θ k=
φ k+ 3 π/4, output symbol is
;
If initial phase
φ k=0, signal strength signal intensity is 1; Input bit pattern (X, Y) is carried out to mapping code, X input 0 is expressed as+1, X input 1 is expressed as-1; Y input 0 is expressed as+1, Y input 1 is expressed as-1; The modulation formula of inputting bit pattern (X, Y) is: S=cos
θ k+ j × sin
θ k=X+j × Y.
Constellation point under described D8PSK pattern distributes, and input bit pattern (X, Y, Z) is mapped as a symbol in constellation point, and its mapping mode is just existing mapped mode planisphere difference eight phase phase shifts, the mapped mode planisphere after being improved; The variation of its output phase is as follows,
When input code flow is 000, its output phase
θ k=
φ k+ π/8, output symbol is
,
When input code flow is 001, its output phase
θ k=(
φ k+ 15 π)/8, output symbol is
,
When input code flow is 010, its output phase
θ k=(
φ k+ 3 π)/8, output symbol is
,
When input code flow is 011, its output phase
θ k=(
φ k+ 13 π)/8, output symbol is
,
When input code flow is 100, its output phase
θ k=(
φ k+ 7 π)/8, output symbol is
,
When input code flow is 101, its output phase
θ k=(
φ k+ 9 π)/8, output symbol is
,
When input code flow is 110, its output phase
θ k=(
φ k+ 5 π)/8, output symbol is
,
When input code flow is 111, its output phase
θ k=(
φ k+ 11 π)/8, output symbol is
;
If initial phase
φ k=0, signal strength signal intensity is 1; When X is 0 and Z while being 0, input bit pattern (X, Z) is expressed as+1, and when X is 1 and Z while being 1, input bit pattern (X, Z) is expressed as-1; Input bit pattern (Y) is 0 to be expressed as π/8, and input bit pattern (Y) is 1 to be expressed as
π/8; The modulation formula of inputting bit pattern (X, Y, Z) can be expressed as: S=cos
θ k+ j × sin
θ k=X × cos (Y)+j × Z × sin (Y).
After the present invention improves, according to signal to noise ratio, the modulation system of every sub-channels is carried out to adaptive adjustment, carry out corresponding demodulation at receiving terminal, solve following problem:
1. adaptive modulation and coding mode, to the modulation system of the serious subchannel employing strong robustness of noise jamming, to strengthen its antijamming capability.
2. determine modulation and coded system according to the signal to noise ratio of subchannel, ensure that the subchannel that signal to noise ratio is high distributes higher transmission power and the modulation system that adopts high transfer rate.
3. adaptive modulation and coding mode, has improved efficiency of transmission and the antijamming capability of whole system.
Brief description of the drawings
Fig. 1 is transmitting terminal composition schematic diagram of the present invention.
Fig. 2 is receiving terminal composition schematic diagram of the present invention.
Fig. 3 is adaptive modulation and coding method block diagram of the present invention.
Fig. 4 is DBPSK pattern planisphere of the present invention.
Fig. 5 is DQPSK pattern planisphere of the present invention.
Fig. 6 is D8PSK pattern planisphere of the present invention.
Embodiment
OFDM power carrier physical layer is directly towards the actual physical medium power line of bearing transfer of data, the physical connection that a transmission original bit stream is provided for last layer MAC layer on power line, so physical layer is directly faced various interference and the decay of power line.
Below in conjunction with accompanying drawing, the invention will be further described.
As shown in Figure 1, physical layer transmitting terminal of the present invention comprises forward error controlled encoder and OFDM modulation module.Data to be transmitted is first crosstalked, RS coding, and convolutional encoding, interleaving treatment, then carry out Adaptive Modulation and send to and do IFFT conversion.
Part before IFFT is called baseband system.First the data of input are carried out to forward direction error correction and detection (Forward error correction) coding, FEC is made up of Reed Solomon coding and convolutional encoding; After convolutional encoding, it is the interweaving encoding module of a bidimensional.The object interweaving is protection signal transmission, resists two kinds of different interference and decline: one is that burst error is disturbed, and another kind is frequency deep fade.Data-signal carries out subcarrier Adaptive Modulation according to previous test data channel estimating information after interweaving.
The link baseband architecture of the receiving terminal corresponding with physical layer transmitting terminal of the present invention as shown in Figure 2.This link is just in time contrary with transmitting terminal link, and the data after FFT conversion are carried out demapping, and multi-system data bit is become to 2 system data code flows, carry out afterwards deinterleaving, Viterbi decoding, and the solution processing of crosstalking, finally obtains the discernible data of MAC layer.
The following describes adaptive modulation and coding principle of the present invention.
As shown in Figure 3, first the present invention carries out serial to parallel conversion to the data after interweaving, and serial data stream is become to parallel data flow; Then according to the descending lead data channel estimation results of previous frame, signal to noise ratio and predefined comparison threshold that subchannel is estimated compare; Then determine the modulation system of subchannel according to comparative result; Finally carry out sub-channel modulation.
1. the setting of subchannel signal to noise ratio comparison threshold and modulation system are determined
In above-mentioned adaptive modulation and coding process, more crucial is the setting of comparison threshold.General threshold value is adjustable in engineering application.The comparison threshold that the present invention sets is as shown in table 1.The present invention, according to these comparison thresholds, determines sub-channel modulation mode.In the time of be less than-5dB of subchannel signal to noise ratio, determine the modulating mode with ROBO; As be more than or equal to-5dB of subchannel signal to noise ratio and while being less than 0dB, determine the modulation system with DBPSK; In the time that subchannel signal to noise ratio is more than or equal to 0dB and is less than 5dB, determine the modulation system with DQPSK; In the time that subchannel signal to noise ratio is more than or equal to 5dB, determine the modulation system with D8PSK.
Table 1:
2. sub-channel modulation
Subchannel is modulated accordingly and encodes after determining modulation system.DBPSK, the planisphere of DQPSK and D8PSK is as follows
For simplicity, analyze and remove Gray code conversion and absolute code conversion.
The mapping mode of DBPSK pattern as shown in Figure 4, the relation between input code flow and output phase is as shown in table 2.
Table 2:
If initial phase
φ k=0, signal strength signal intensity is 1, and input bit pattern (X) is carried out to mapping code, input 0 and is expressed as-1, input 1 to be expressed as+1, the modulation formula of inputting bit pattern (X) is: S=cos
θ k+ j × sin
θ k=X.
At output solution timing, demodulate input code flow according to the real part of S and imaginary part:
bit0?=?real(S)，
There is certain logical relation in the input code flow after demodulation and actual input code flow, the bit0 demodulating does not carry out hard decision, directly sends into Viterbi decoder and carry out soft-decision, can well recover original input code flow.
The mapping mode of DQPSK pattern as shown in Figure 5, the relation between input code flow and output phase: as shown in table 3.
Table 3:
If initial phase
φ k=0, signal strength signal intensity is 1; Input bit pattern (X, Y) is carried out to mapping code, X input 0 is expressed as+1, X input 1 is expressed as-1; Y input 0 is expressed as+1, Y input 1 is expressed as-1; The modulation formula of inputting bit pattern (X, Y) is: S=cos
θ k+ j × sin
θ k=X+j × Y.
At output solution timing, demodulate input code flow according to the real part of S and imaginary part:
bit0?=?real(S)，
bit1?=?imag(S)；
There is certain logical relation in the input code flow after demodulation and actual input code flow, the bit0 demodulating and bit1 do not carry out hard decision, directly sends into Viterbi decoder and carry out soft-decision, can well recover original input code flow.
The mapping mode of D8PSK pattern as shown in Figure 6, the relation between input code flow and output phase is as shown in table 4.
If initial phase
φ k=0, signal strength signal intensity is 1; When X is 0 and Z while being 0, input bit pattern (X, Z) is expressed as+1, and when X is 1 and Z while being 1, input bit pattern (X, Z) is expressed as-1; Input bit pattern (Y) is 0 to be expressed as π/8, and input bit pattern (Y) is 1 to be expressed as
π/8; The modulation formula of inputting bit pattern (X, Y, Z) can be expressed as: S=cos
θ k+ j × sin
θ k=X × cos (Y)+j × Z × sin (Y).
At output solution timing, according to the real part of S and imaginary part demodulation input code flow:
bit0?=?real(S)；
bit1?=abs(real(S))-abs(imag(S))；
bit2?=?imag(S)；
There is certain logical relation in the input code flow after demodulation and actual input code flow, bit0, the bit1 demodulating and bit2 all do not carry out hard decision, directly send into Viterbi decoder and carry out soft-decision, can well recover original input code flow.
Table 4:
Below in conjunction with specific embodiment, the present invention is described further.
The present invention includes following steps:
Step 1, input code flow is through forward error correction coder, input value serial-parallel converter;
Step 2, serial data is converted to parallel code stream by serial-parallel converter;
Step 3, sets up comparison threshold, comprise-5dB of these comparison threshold values, 0dB, 5dB;
Step 4, compares the comparison threshold value of the signal to noise ratio of sub-carrier channels valuation gained and step 3; And determine sub-channel modulation pattern according to this comparative result;
Step 5, carries out sub-channel modulation according to definite sub-channel modulation pattern.
Claims (6)
1. an AMI system carrier communication module adaptive modulation and coding method, the method comprises the steps:
Step 1, input code flow, through forward error correction coder, inputs to serial-parallel converter;
Step 2, serial data is converted to parallel code stream by serial-parallel converter;
Step 3, sets up comparison threshold, and sub-carrier channels valuation and this comparison threshold are compared;
Step 4, subchannel is determined sub-channel modulation pattern according to the comparative result of step 3;
Step 5, carries out sub-channel modulation according to definite sub-channel modulation pattern.
2. AMI system carrier communication module adaptive modulation and coding method according to claim 1, is characterized in that, described sub-carrier channels valuation is for obtaining the signal to noise ratio of subchannel.
3. AMI system carrier communication module adaptive modulation and coding method according to claim 2, is characterized in that comprise-5dB of described comparison threshold, 0dB, 5dB; In the time of be less than-5dB of subchannel signal to noise ratio, determine the modulating mode with ROBO; As be more than or equal to-5dB of subchannel signal to noise ratio and while being less than 0dB, determine the modulation system with DBPSK; In the time that subchannel signal to noise ratio is more than or equal to 0dB and is less than 5dB, determine the modulation system with DQPSK; In the time that subchannel signal to noise ratio is more than or equal to 5dB, determine the modulation system with D8PSK.
4. AMI system carrier communication module adaptive modulation and coding method according to claim 3, it is characterized in that, constellation point under described DBPSK pattern distributes, input bit pattern (X) is mapped as a symbol in constellation point, its mapping mode is by existing mapped mode planisphere difference two-phase phase shift, the mapped mode planisphere after being improved; The variation of its output phase is as follows,
When input code flow is 1, its output phase
θ k=
φ k, output symbol is+1,
When input code flow is-1, its output phase
θ k=
φ k+ π, output symbol is-1;
Input bit pattern (X) is carried out to mapping code, input 0 and be expressed as-1, input 1 be expressed as+1, the modulation formula of inputting bit pattern (X) is: S=cos
θ k+ j × sin
θ k=X.
5. AMI system carrier communication module adaptive modulation and coding method according to claim 3, it is characterized in that, constellation point under described DQPSK pattern distributes, input bit pattern (X, Y) be mapped as a symbol in constellation point, its mapping mode is by existing mapped mode planisphere difference four phase phase shifts, the mapped mode planisphere after being improved; The variation of its output phase is as follows,
When input code flow is 00, its output phase
θ k=
φ k+ π/4, output symbol is
,
When input code flow is 01, its output phase
θ k=
φ k+ 7 π/4, output symbol is
,
When input code flow is 11, its output phase
θ k=
φ k+ 5 π/4, output symbol is
,
When input code flow is 10, its output phase
θ k=
φ k+ 3 π/4, output symbol is
;
If initial phase
φ k=0, signal strength signal intensity is 1; Input bit pattern (X, Y) is carried out to mapping code, X input 0 is expressed as+1, X input 1 is expressed as-1; Y input 0 is expressed as+1, Y input 1 is expressed as-1; The modulation formula of inputting bit pattern (X, Y) is: S=cos
θ k+ j × sin
θ k=X+j × Y.
6. AMI system carrier communication module adaptive modulation and coding method according to claim 3, it is characterized in that, constellation point under described D8PSK pattern distributes, input bit pattern (X, Y, Z) be mapped as a symbol in constellation point, its mapping mode is just existing mapped mode planisphere difference eight phase phase shifts, the mapped mode planisphere after being improved; The variation of its output phase is as follows,
When input code flow is 000, its output phase
θ k=
φ k+ π/8, output symbol is
,
When input code flow is 001, its output phase
θ k=(
φ k+ 15 π)/8, output symbol is
,
When input code flow is 010, its output phase
θ k=(
φ k+ 3 π)/8, output symbol is
,
When input code flow is 011, its output phase
θ k=(
φ k+ 13 π)/8, output symbol is
,
When input code flow is 100, its output phase
θ k=(
φ k+ 7 π)/8, output symbol is
,
When input code flow is 101, its output phase
θ k=(
φ k+ 9 π)/8, output symbol is
,
When input code flow is 110, its output phase
θ k=(
φ k+ 5 π)/8, output symbol is
,
When input code flow is 111, its output phase
θ k=(
φ k+ 11 π)/8, output symbol is
;
If initial phase
φ k=0, signal strength signal intensity is 1; When X is 0 and Z while being 0, input bit pattern (X, Z) is expressed as+1, and when X is 1 and Z while being 1, input bit pattern (X, Z) is expressed as-1; Input bit pattern (Y) is 0 to be expressed as π/8, and input bit pattern (Y) is 1 to be expressed as
π/8; The modulation formula of inputting bit pattern (X, Y, Z) can be expressed as: S=cos
θ k+ j × sin
θ k=X × cos (Y)+j × Z × sin (Y).
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| CN105591716B (en) * | 2014-12-26 | 2018-10-09 | 青岛海信日立空调系统有限公司 | A kind of serial data communication method, apparatus and system based on single carrier |
| CN105336147B (en) * | 2015-10-21 | 2018-08-24 | 宁波三星医疗电气股份有限公司 | Method for power consumer adaptive multi-carrier modulation system meter reading |
| CN105846971A (en) * | 2016-03-21 | 2016-08-10 | 浙江大学 | Anti-interference self-adaptive coding and decoding method in wireless transmission |
| CN106161310B (en) * | 2016-07-21 | 2019-05-17 | 南京邮电大学 | A kind of multicarrier difference chaotic shift keying modulation demodulation method and modem |
| CN107070838B (en) * | 2017-04-18 | 2020-03-31 | 河南许继仪表有限公司 | ROBO coding modulation and demodulation method based on G3-PLC frequency domain |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102202030A (en) * | 2011-03-25 | 2011-09-28 | 北京智网能达科技有限公司 | Data transmission system and method suitable for wired and wireless fusion of AMI (Advanced Metering Infrastructure) |
| CN102970268A (en) * | 2012-11-27 | 2013-03-13 | 陕西天思信息科技有限公司 | OFDM (Orthogonal Frequency Division Multiplexing) adaptive modulation system for EOC (Ethernet Over Coax) device |
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2013
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Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102202030A (en) * | 2011-03-25 | 2011-09-28 | 北京智网能达科技有限公司 | Data transmission system and method suitable for wired and wireless fusion of AMI (Advanced Metering Infrastructure) |
| CN102970268A (en) * | 2012-11-27 | 2013-03-13 | 陕西天思信息科技有限公司 | OFDM (Orthogonal Frequency Division Multiplexing) adaptive modulation system for EOC (Ethernet Over Coax) device |
Non-Patent Citations (1)
| Title |
|---|
| 李风飞，刘光熹，胡国荣.适用于AMI的无线有线融合数据传输方法.《电视技术》.2012,第36卷(第19期),15-16页，第2节系统设计，图3. * |
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