CN103117766B - Electronic device and transmitter DC offset calibration method - Google Patents
Electronic device and transmitter DC offset calibration method Download PDFInfo
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- CN103117766B CN103117766B CN201210461847.0A CN201210461847A CN103117766B CN 103117766 B CN103117766 B CN 103117766B CN 201210461847 A CN201210461847 A CN 201210461847A CN 103117766 B CN103117766 B CN 103117766B
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Abstract
The invention provides an electronic device and a transmitter DC offset calibration method thereof. The electronic device includes a digital-to-analog converter (DAC), a transmitter front-end (TX FE), an amplifier, an analog-to-digital converter (ADC), and a swap circuitry. The DAC has a first and a second output end. The TX FE has a first and a second input end coupled to the first and the second output end of the DAC, respectively. The ADC has a first and a second input end coupled to a first and a second output end of the amplifier, respectively. The swap circuitry is configured to couple the first and second output ends of the DAC to a first and a second input end of the amplifier in a normal state, respectively, and couple the first and second output ends of the DAC to the second and first input ends of the amplifier in a swapped state, respectively.
Description
[technical field]
The present invention has about a kind of electronic installation, and the DC offset calibration method of reflector relating to a kind of electronic installation especially and performed by this electronic installation.
[background technology]
In order to communicate with another electronic installation; one electronic installation (such as mobile phone, panel computer, notebook computer or multi-media player) can comprise a digital baseband circuit usually; one digital to analog converter (DAC); and transmitter front-end (transmitter front-end, a TX FE) circuit.In simple terms, this digital baseband circuit first produces a digital signal, then this digital signal is converted to a fundamental frequency signal by DAC, then this this fundamental frequency signal of TX FE circuit up-conversion is to produce a radio frequency (RF) signal, and amplifies this RF signal and the RF signal after this amplification is sent to an antenna for transmitting.For example, this TX FE circuit can comprise following element: one for generation of the local oscillator (LO) of carrier signal; One for by this fundamental frequency signal of mixing and this carrier signal to produce the frequency mixer of this RF signal; And one for amplifying the gain-programmed amplifier (programmable gain amplifier, PGA) of this RF signal.
An analog signal on above-mentioned transmission path may have some direct currents (DC) skew.Little DC skew can be ignored, but if DC skew is comparatively large, then can have influence on the quality of communication.Therefore in order to prevent the reduction of communication quality, DC skew must obtain suitable calibration.
[summary of the invention]
In view of this, the invention provides a kind of electronic installation and reflector DC offset calibration method, to solve foregoing problems.
The embodiment of the present invention provides a kind of electronic installation, comprising: digital to analog converter, has the first output and the second output; Transmitter front-end circuit, has and is coupled to the first output of this digital to analog converter and the first input end of the second output and the second input respectively; Amplifier, has first input end, the second input, the first output and the second output; Analog to digital converter, has and is coupled to the first output of this amplifier and the first input end of the second output and the second input respectively; And switched circuit, for time in normal operation, using the first output of this digital to analog converter and the second output as the first output of this switched circuit and the second output to be coupled to first input end and second input of this amplifier respectively, and when exchanging under operating state, using the first output of this digital to analog converter and the second output as the second output of this switched circuit and the first output to be coupled to the second input and the first input end of this amplifier respectively.
The embodiment of the present invention provides a kind of reflector DC offset calibration method, performed by an electronic installation, this electronic installation comprises digital to analog converter, is coupled to the transmitter front-end circuit of this digital to analog converter, amplifier, be coupled to the analog to digital converter of this amplifier, and the method comprises: the first input end and the second input that the first output of this digital to analog converter and the second output are coupled to respectively this amplifier; There is provided a special value for this digital to analog converter and obtain the first numerical value from this analog to digital converter; First output of this digital to analog converter and the second output are coupled to respectively the second input and the first input end of this amplifier; There is provided this special value for this digital to analog converter and obtain second value from this this analog to digital converter; According to this first numerical value and second value, the reflector direct current offset to this electronic installation is calibrated.
The embodiment of the present invention provides a kind of electronic installation, comprise: transmission path, RX path and switching circuit, this switching circuit is coupled to this transmission path and this RX path, for disconnecting the connection between this transmission path and this RX path when this electronic installation is in normal mode; And when this electronic installation is in reflector DC bias criterion pattern, the baseband portion coupling this transmission path to the baseband portion of this RX path to form a base band loop.
The electronic installation of the embodiment of the present invention and reflector DC offset calibration method can be calibrated the DC skew of reflector on the basis saving hardware cost.
For making the above-mentioned purpose of the present invention, feature and advantage become apparent, special embodiment below, and coordinate accompanying drawing, be described in detail as follows.
[accompanying drawing explanation]
Fig. 1 is the simplification module diagram of a kind of electronic installation according to the embodiment of the present invention;
Figure 2 shows that the schematic flow sheet of the calibration steps that the electronic installation of the embodiment of the present invention runs;
Figure 3 shows that a kind of principle of equal effects schematic diagram when electronic installation 100 of the embodiment of the present invention is in TX DC bias criterion pattern;
Figure 4 shows that the another kind of principle of equal effects schematic diagram when electronic installation 100 of the embodiment of the present invention is in TX DC bias criterion pattern.
[embodiment]
Fig. 1 is the simplification module diagram of a kind of electronic installation 100 according to the embodiment of the present invention.One of characteristic of this electronic installation 100 is that it can communicate with another electronic installation.For example, this electronic installation 100 can be a mobile phone, panel computer, notebook computer, multi-media player or with WAP (wireless access point) (access point, AP).In the present embodiment, this electronic installation 100 comprises at least one digital circuit 110, one digital to analog converter (DAC) 120, one switched circuit 130, one multiplexer (MUX) 135, one amplifier 140, analog to digital converter (ADC) 150, one transmitter front-end (TX FE) circuit 160, and a receiver front end (RX FE) circuit 170.In order to avoid the teaching of mistake, other elements that this electronic installation 100 comprises are not shown in Figure 1.
This digital circuit 110 can be a baseband circuit and have output 112 and an input 111.This output 112 exports ∑-△ modulator (sigma-delta modulator, SDM) 119 digital signal produced by this digital circuit 110.This ∑-△ modulator 119 performs ∑-△ modulation operations to produce this digital signal, and this digital signal is inputed to DAC 120.Via ∑-△ modulation operations, be equivalent to the resolution that SDM119 increases DAC 120 equivalently.It should be noted that in another embodiment of the present invention, SDM 119 is omissible.
This DAC 120 and TX FE circuit 160 form transmission path, and wherein DAC 120 is as baseband portion.This RX FE circuit 170, amplifier 140 and ADC 150 form RX path, and wherein amplifier 140 and ADC 150 are as baseband portion.This electronic installation 100 can also comprise other transmission path and/or RX path (not shown in Figure 1).This switched circuit 130 forms a switching circuit with this MUX 135.
DAC 120 has an input 121 and pair of output 122.This input 121 couples the output 112 with this digital circuit 110.This TX FE circuit 160 has a pair input 161, is coupled to the pair of output 122 of DAC 120 respectively.This switched circuit 130 has a pair input 131 and pair of output 132.This input 131 is coupled to the pair of output 122 of DAC 120 respectively.RX FE circuit 170 has pair of output 172.This MUX 135 has first pair of input, 136, second pair of input 137 and pair of output 138.This first pair of input 136 is coupled to the pair of output 132 of switched circuit 130 respectively.This second pair of input 137 is coupled to the pair of output 172 of RX FE circuit 170 respectively.This amplifier 140 is differential amplifiers and has a pair input 141 and pair of output 142.Wherein this pair input 141 is coupled to the pair of output 138 of MUX 135 respectively.ADC 150 has a pair input 151 and an output 152.This pair input 151 is coupled to the pair of output 142 of amplifier 140 respectively.This output 152 is coupled to the input 111 of digital circuit 110.
TX FE circuit 160 can also comprise following element: for generation of the first local oscillator of first carrier signal; Carry out mixing for the first baseband signal that DAC 120 is exported and this first carrier signal and produce the first frequency mixer of a RF signal; And for amplifying the gain-programmed amplifier of a RF signal.RF signal after this amplification is then transferred into the antenna of electronic installation 100 for transmitting.This RX TE circuit 170 can comprise following element: for generation of the second local oscillator of the second carrier signal, for the low noise amplifier (LNA) of the 2nd RF signal that the antenna amplified via electronic installation 100 receives, and for mixing the 2nd RF signal and this second carrier signal to produce the second frequency mixer of the second baseband signal.This second baseband signal then can be sent to amplifier 140.This amplifier 140 can be the amplifier that a gain-programmed amplifier or has high-gain, its can on electronic installation 100 pairs of transmission paths DC skew judge while as an integrator.This electronic installation 100 can also comprise a TX filter and a RX filter, wherein this TX filter was used for before the first baseband signal is sent to TX FE circuit 160 and/or switched circuit 130, filtering is carried out to this first baseband signal, and this RX filter is used for carrying out filtering to this second baseband signal before the second baseband signal is sent to MUX 135.
This MUX 135 can make some device element in electronic installation 100 be shared by multiplexing mode.Such as, this electronic installation 100 can have normal mode and reflector direct current (TX DC) bias criterion pattern, and this amplifier 140 can be shared with ADC 150 under above-mentioned two kinds of patterns.When electronic installation 100 is in normal mode, MUX 135 connects RX FE circuit 170 to amplifier 140.In such a mode, RX FE circuit 170, amplifier 140, and ADC 150 runs the RX path (I path or Q path) as electronic installation 100.In addition, DAC 120 and TX FE circuit 160 run the transmission path (I path or Q path) as electronic installation 100.This RX path and this transmission path disconnect connection to each other via this MUX135, thus this electronic installation 100 can be made to communicate with another electronic installation, and this another electronic installation can be such as a base station or a wireless aps.In theory, when electronic installation 100 is in normal mode, this switched circuit 130 can not have influence on the running of electronic installation 100, and no matter switched circuit 130 is in normal operating conditions or swap status and all can not produces it and interfere.
When electronic installation 100 is in TX DC bias criterion pattern, switched circuit 130 can be connected to amplifier 140 by this MUX 135.In such a mode, this DAC 120, switched circuit 130, MUX 135, amplifier 140 and ADC 150 can form a base band loop of electronic installation 100.Because the signal transmitted in this loop is positioned at base band domain and can not enters into RF territory, therefore in other words, electronic installation 100 has a base band winding and arranges when TX DC bias criterion pattern.
Figure 2 shows that the schematic flow sheet of the calibration steps that the electronic installation 100 of the embodiment of the present invention runs.The electronic installation 100 that Fig. 3 and Fig. 4 is depicted as the embodiment of the present invention is respectively in principle of equal effects schematic diagram during TX DC bias criterion pattern.For simplicity, MUX 135, TX FE 160 and RX FE 170 be not shown in above-mentioned two figure.Also show switched circuit 130 in above-mentioned two figure and can comprise four switches 331,332,333 and 334.Its breaker in middle 331 is coupled to first input end 131a and the first output 132a of this switched circuit 130; Switch 332 is coupled to first input end 131a and the second output 132b of switched circuit 130; Switch 333 is coupled to the second input 131b and the first output 132a of switched circuit 130; Switch 334 is coupled to the second input 131b and the second output 132b of this switched circuit 130.In Fig. 3, switching circuit 130 is in a normal operating conditions, and in Fig. 4, switching circuit 130 is in an exchange operating state.In addition, Fig. 3 and Fig. 4 also depicts three voltage sources 321,341 and 351.Above-mentioned three voltage sources the actual element of inverter circuit, it is only for representing the equivalent DC skew of each position in the base band domain of electronic installation 100.
Step 210,220,230 and 240 is performed when electronic installation 100 is in TX DC bias criterion pattern.As previously mentioned, when electronic installation 100 is under this pattern, switched circuit 130 can be in normal operating conditions or exchange operating state.Owing to not using amplifier 140 and ADC150 in RX FE circuit 170, therefore this amplifier 140 and ADC 150 are available and may be used for judging that the DC in the transmission path of electronic installation 100 offsets.
In step 210, the first output 122a of this DAC 120 and the second output 122b is coupled to first input end 141a and the second input 141b of amplifier 140 by this switched circuit 130 and this MUX 135 respectively.Then, in step 220, this digital circuit 110 provides a specific numerical value for DAC 120 and obtains the first numerical value D1 from ADC 150.As shown in Figure 3, in step 210 and 220, this switched circuit 130 is in normal operating conditions, and switch 331 and 334 is opened, and switch 332 and 333 cuts out.
Offset VOS, VOS1 and VOS2 owing to the differential lines shown in Fig. 3 may have DC, although therefore when above-mentioned special value is zero, this first numerical value D1 can be still a nonzero value.Especially, when above-mentioned special value is zero, this first numerical value D1 can with VOS+VOS1+ (VOS2/G) proportional relation, wherein G is the gain of amplifier 140.Because G is relatively large, therefore (VOS2/G) is then relatively little, even negligible.
In step 230, the first output 122a of DAC 120 and the second output 122b is coupled to the second input 141b and the first input end 141a of amplifier 140 by this switched circuit 130 and MUX 135 respectively.Then, in step 240, this digital circuit 110 provides special value to DAC 120, and from ADC150 acquisition one second value D2.As shown in Figure 4, in step 230 and 240, this switched circuit 130 is in exchange operating state, and switch 331 and 334 cuts out, and switch 332 and 333 is opened.
Because above-mentioned DC offsets the existence of VOS, VOS1 and VOS2, this second value D2 can be a nonzero value, although when above-mentioned special value is zero.Especially, when above-mentioned special value is zero, this second value D2 can with-VOS+VOS1+ (VOS2/G) proportional relation.Because G is relatively large, therefore (VOS2/G) is then relatively little, even negligible.
Step 250 is performed when electronic installation 100 is in normal mode.When electronic installation 100 is under this pattern, DAC 120 and TX FE circuit 160 can be used as the transmission path of circuit arrangement 100.In step 250, digital circuit 110 offsets VOS according to this first numerical value D1 and second value D2 to the DC of electronic installation 100 and calibrates.Such as, if when above-mentioned special value is zero, this digital circuit 110 can by deducting D2 and obtain third value D3 in D1, and the proportional relation of this third value D3 and VOS and irrelevant in fact with VOS1 and VOS2.Based on this third value D3, digital circuit 110 can offset VOS to DC and calibrate under numeric field.Such as, this digital circuit 110 can increase in a deviant to each digital value above-mentioned, and inputs in DAC 120 with canceling DC offset VOS.This deviant can relation proportional with-D3.Offset the impact of VOS owing to can not be subject to DC, this transmission path (i.e. DAC 120 and TX FE circuit 160) can obtain better reliability performance.
The TX DC offset calibration mechanism of the embodiment of the present invention has many-sided advantage.When electronic installation 100 is in TX DC bias criterion pattern, the differential signal produced by DAC 120 directly by switched circuit 130 with MUX 135 loopback to amplifier 140, and RF territory can not be entered to.This base band winding arranges and the elapsed time of aforesaid DC offset calibration program is reduced relatively.In addition, this set slow down the demand of the accuracy to ADC 150.Especially, although ADC 150 does not possess high-resolution, digital circuit 110 also accurately can balance out a part of DC and offset VOS.In addition, this electronic installation 100 makes the amplifier 140 in RX path can be reused in TX DC bias criterion pattern with ADC 150.Therefore, except some the extra hardware costs needing consumption relevant with MUX 135 with switched circuit 130, the embodiment of the present invention can save hardware cost.In addition, when electronic installation 100 is arranged in terminal use's hand, this TX DC offset calibration still can perform offset calibration program.The communication quality that this point makes electronic installation 100 still can maintain after have left manufacturer/distributors.
Although the present invention discloses as above with preferred embodiment; so itself and be not used to limit the present invention; any person skilled in the art; without departing from the spirit and scope of the present invention; when doing a little change and retouching, the scope that therefore protection scope of the present invention ought define depending on claims of the present invention is as the criterion.
Claims (13)
1. an electronic installation, is characterized in that, comprising:
Digital to analog converter, has the first output and the second output;
Transmitter front-end circuit, has and is coupled to the first output of this digital to analog converter and the first input end of the second output and the second input respectively;
Amplifier, has first input end, the second input, the first output and the second output;
Analog to digital converter, has and is coupled to the first output of this amplifier and the first input end of the second output and the second input respectively;
Switched circuit, for time in normal operation, using the first output of this digital to analog converter and the second output as the first output of this switched circuit and the second output to be coupled to first input end and second input of this amplifier respectively, and when exchanging under operating state, using the first output of this digital to analog converter and the second output as the second output of this switched circuit and the first output to be coupled to the second input and the first input end of this amplifier respectively; And
Digital circuit, be coupled to the input of this digital to analog converter and the output of this analog to digital converter, this digital circuit is used for: when this switched circuit is under this normal operating conditions for this digital to analog converter provides a special value, and obtain the first numerical value from this analog to digital converter; When this switched circuit is under this exchange operating state for this digital to analog converter provides this special value, and obtain second value from this analog to digital converter; And the direct current offset to this electronic installation is calibrated according to this first numerical value and second value.
2. electronic installation according to claim 1, is characterized in that, also comprises:
Receiver front end circuit, has the first output and the second output;
Multiplexer, for when this electronic installation is in normal mode, first output of this receiver front end circuit and the second output are coupled to respectively first input end and second input of this amplifier, and when this electronic installation is in reflector DC bias criterion pattern, the first output of this switched circuit and the second output are coupled to respectively first input end and second input of this amplifier.
3. electronic installation according to claim 1, is characterized in that, this digital circuit comprises:
Sigma-delta modulator, has an output of the input being coupled to this digital to analog converter.
4. a reflector DC offset calibration method, performed by an electronic installation, it is characterized in that, this electronic installation comprises digital to analog converter, is coupled to the transmitter front-end circuit of this digital to analog converter, amplifier, be coupled to the analog to digital converter of this amplifier, the method comprises:
First output of this digital to analog converter and the second output are coupled to respectively first input end and second input of this amplifier;
There is provided a special value for this digital to analog converter and obtain the first numerical value from this analog to digital converter;
First output of this digital to analog converter and the second output are coupled to respectively the second input and the first input end of this amplifier;
There is provided this special value for this digital to analog converter and obtain second value from this analog to digital converter;
According to this first numerical value and second value, the reflector direct current offset to this electronic installation is calibrated.
5. calibration steps according to claim 4, is characterized in that, this electronic installation also comprises:
Switched circuit, for in normal operation the first output of this digital to analog converter and the second output being coupled to respectively first input end and second input of this amplifier, and exchanging the second input and the first input end that under operating state, the first output of this digital to analog converter and the second output are coupled to respectively this amplifier.
6. calibration steps according to claim 5, is characterized in that, wherein this electronic installation also comprises a receiver front end circuit, and the method also comprises:
When this electronic installation is in normal mode, the first output of this receiver front end circuit and the second output are coupled to respectively first input end and second input of this amplifier.
7. calibration steps according to claim 4, is characterized in that, this electronic installation also comprises sigma-delta modulator, has an output of the input being coupled to this digital to analog converter.
8. an electronic installation, is characterized in that, comprising:
Transmission path;
RX path;
Switching circuit, is coupled to this transmission path and this RX path, for:
The connection between this transmission path and this RX path is disconnected when this electronic installation is in normal mode;
When this electronic installation is in reflector DC bias criterion pattern, the baseband portion coupling this transmission path to the baseband portion of this RX path to form a base band loop; And
One digital circuit, be coupled to the input in this base band loop and the output in this base band loop, and this digital circuit is used for: when this electronic installation is in reflector DC bias criterion pattern, when this switching circuit is under normal operating conditions for the input in this base band loop provides a special value, to obtain the first numerical value from the output in this base band loop; When this switching circuit is under exchange operating state for the input in this base band loop provides this special value, and obtain second value from the output in this base band loop; And when this electronic installation is in normal mode according to this first numerical value and second value the direct current offset to this electronic installation calibrate.
9. electronic installation according to claim 8, is characterized in that, the baseband portion of this transmission path comprises a digital to analog converter, and the baseband portion of this RX path comprises an amplifier and is coupled to the analog to digital converter of this amplifier.
10., according to the electronic installation described in claim 9, it is characterized in that, this switching circuit comprises:
Switched circuit, for under this normal operating conditions using the first output of this digital to analog converter and the second output as the first output of this switched circuit and the second output to be coupled to first input end and second input of this amplifier respectively, and under this exchange operating state using the first output of this digital to analog converter and the second output as the second output of this switched circuit and the first output to be coupled to the second input and the first input end of this amplifier respectively.
11. according to the electronic installation described in claim 10, and it is characterized in that, this RX path also comprises a receiver front end circuit, and this switching circuit also comprises:
Multiplexer, for when this electronic installation is in normal mode, first output of this receiver front end circuit and the second output are coupled to respectively first input end and second input of this amplifier, and when this electronic installation is in reflector DC bias criterion pattern, the first output of this switched circuit and the second output are coupled to respectively first input end and second input of this amplifier.
12. electronic installations according to claim 10, is characterized in that, also comprise a digital circuit, and be coupled to the input of this digital to analog converter and the output of this analog to digital converter, wherein this digital circuit is used for:
When this switched circuit is under this normal operating conditions for this digital to analog converter provides a special value, and obtain the first numerical value from this analog to digital converter;
When this switched circuit is under this exchange operating state for this digital to analog converter provides this special value, and second value should be obtained from this analog to digital converter; And
According to this first numerical value and second value, the direct current offset to this electronic installation is calibrated.
13. electronic installations according to claim 12, is characterized in that, this digital circuit comprises:
Sigma-delta modulator, has an output of the input being coupled to this digital-to-analogue conversion.
Applications Claiming Priority (4)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US201161560420P | 2011-11-16 | 2011-11-16 | |
| US61/560,420 | 2011-11-16 | ||
| US13/610,808 US8659456B2 (en) | 2011-11-16 | 2012-09-11 | Electronic device and transmitter DC offset calibration method thereof |
| US13/610,808 | 2012-09-11 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN103117766A CN103117766A (en) | 2013-05-22 |
| CN103117766B true CN103117766B (en) | 2015-03-25 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201210461847.0A Expired - Fee Related CN103117766B (en) | 2011-11-16 | 2012-11-16 | Electronic device and transmitter DC offset calibration method |
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| Country | Link |
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| CN (1) | CN103117766B (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104253780B (en) * | 2013-06-27 | 2017-07-28 | 鸿富锦精密工业（深圳）有限公司 | Direct-current offset calibration circuit |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1446421A (en) * | 2000-08-04 | 2003-10-01 | 摩托罗拉公司 | Apparatus for reducing DC offset in receiver |
| US20040043744A1 (en) * | 2002-08-29 | 2004-03-04 | Nikolai Schlegel | Apparatus and method for DC offset compensation in a direct conversion receiver |
| US20100119008A1 (en) * | 2008-11-11 | 2010-05-13 | Flexiradio, Llc | Programmable wide band digital receiver/transmitter |
| CN101753101A (en) * | 2008-12-16 | 2010-06-23 | 联发科技股份有限公司 | Amplitude modulation circuit in polar transmitter and method for calibrating amplitude offset in polar transmitter |
-
2012
- 2012-11-16 CN CN201210461847.0A patent/CN103117766B/en not_active Expired - Fee Related
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1446421A (en) * | 2000-08-04 | 2003-10-01 | 摩托罗拉公司 | Apparatus for reducing DC offset in receiver |
| US20040043744A1 (en) * | 2002-08-29 | 2004-03-04 | Nikolai Schlegel | Apparatus and method for DC offset compensation in a direct conversion receiver |
| US20100119008A1 (en) * | 2008-11-11 | 2010-05-13 | Flexiradio, Llc | Programmable wide band digital receiver/transmitter |
| CN101753101A (en) * | 2008-12-16 | 2010-06-23 | 联发科技股份有限公司 | Amplitude modulation circuit in polar transmitter and method for calibrating amplitude offset in polar transmitter |
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| CN103117766A (en) | 2013-05-22 |
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Granted publication date: 20150325 Termination date: 20191116 |