CN102840160A - Air cooling control device and working method thereof - Google Patents
Air cooling control device and working method thereof Download PDFInfo
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- CN102840160A CN102840160A CN2012103697352A CN201210369735A CN102840160A CN 102840160 A CN102840160 A CN 102840160A CN 2012103697352 A CN2012103697352 A CN 2012103697352A CN 201210369735 A CN201210369735 A CN 201210369735A CN 102840160 A CN102840160 A CN 102840160A
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Abstract
The invention relates to an air cooling control device, which comprises a temperature detection sensor, a plurality of fans and a PLC (Programmable Logical Controller) module, wherein the PLC module is connected with the temperature detection sensor, and is suitable for controlling a corresponding quantity of fans to work according to an external temperature. According to the air cooling control device, the PLC module is adopted instead of the conventional relay circuit, so that the defects of complex wiring and high relay failure rate are overcome; and the fan quantity is controlled according to the temperature, the fans can be not started or a small quantity of fans are started in cold winter, and all fans are required to be started for dissipating heat in hot summer, so that a large amount of electric energy is saved, and the service life of a motor is prolonged.
Description
Technical field
The present invention relates to a kind of wind cooling controller and method of work thereof.
Background technique
In the prior art, the transformer of 110kV and following electric pressure often adopts cooling fan that transformer is cooled, and the working condition of cooling fan directly influences the on-load ability of transformer; And air cooling system also breaks down through regular meeting, and through statistics, the air cooling system fault mainly is divided into the control loop element fault; And what the reason of control loop fault mainly was that control unit adopts is electromagnetic relay, and these discrete components reliability that works long hours is not high, and rate of fault is high; Poor anti jamming capability; Cause these elements often to burn, damage, influence the operation of air cooling system, control the technical barrier that the whole wind cooling system is related domain so how to design a kind of electromagnetic relay that replaces.
Summary of the invention
The technical problem that the present invention will solve provides a kind of control gear that is suitable for the testing environment temperature with the control air cooling system.
In order to solve the problems of the technologies described above; The invention provides a kind of wind cooling controller, comprising: temperature detection sensor, plurality of fans, the PLC module that is suitable for just controlling the fan work of respective numbers that links to each other with said temperature detection sensor according to external temperature.
Further, because motor is an inductive load, so in use can cause the wattless power of electrical network to increase; Reduce power factor; So necessary during to fan work, utilize chain type SVG (static reacance generator is also referred to as STATCOM) control gear; Improve the power factor in the electrical network; So described wind cooling controller, also comprise: one is suitable for correcting the chain type SVG control gear of power factor, and this chain type SVG control gear is connected in the input end of the three phase mains of said wind cooling controller.
Further, the H bridge element circuit for the ability auto by pass breaks down to guarantee H electric bridge multi-type multi-electrical level inverter proper functioning, makes said chain type SVG control gear continue to reach the purpose of correcting power factor, and said chain type SVG control gear comprises:
The multi-electrical level inverter of H electric bridge multi-type, it is made up of the three-phase H bridge power model that is connected in said three phase mains, wherein, sets up at least one subsequent use H electric bridge element circuit in every phase H bridge power model; The auto by pass circuit is located at the output terminal of each H electric bridge element circuit, and when a H electric bridge element circuit is damaged, with this H electric bridge element circuit bypass; Sample circuit is suitable for gathering the momentary value of the voltage and current of said three phase mains; Divide the phase current independent controling circuit, it links to each other with said sample circuit is suitable for calculating according to the momentary value of the voltage and current of said three phase mains modulation ratio M and phase angle
of the required sinusoidal modulation wave of said pulse-width modulation circuit; Pulse-width modulation circuit; Link to each other with said minute phase current independent controling circuit, be used for the carrier wave pyramidal wave phase shift SPWM that adopts between each H electric bridge element circuit being controlled according to modulation ratio M and phase angle
of said sinusoidal modulation wave; Promptly; After the H electric bridge element circuit bypass that damages; This pulse-width modulation circuit is suitable on the sampling period basis of invariable that keeps said sample circuit; Change the carrier frequency of said carrier wave pyramidal wave phase shift SPWM of a phase H bridge power model at the H electric bridge element circuit place of this damage, to obtain and this Sampling waveform of corresponding carrier wave pyramidal wave of remaining H electric bridge element circuit quantity phase shift SPWM in H bridge power model mutually.
Further, said minute phase current independent controling circuit comprises:
Phaselocked loop, according to the momentary value of the voltage of said three phase mains to follow the tracks of the voltage-phase of said three phase mains; The given module of wattless current is suitable for calculating the cosine amount of this voltage-phase and multiplying each other with a wattless current reference value according to the voltage-phase that said phaselocked loop draws, to obtain actual wattless current output; The given module of active current; Be suitable for calculating the sinusoidal quantity of this voltage-phase according to the voltage-phase that said phaselocked loop draws; Subtract each other simultaneously and, export to obtain actual active current through multiplying each other with said sinusoidal quantity again after the PI control according to the voltage reference value of the average voltage of the dc bus capacitor of said each phase H bridge power model and a direct current lateral capacitance; The transient current tracking module; Be used for the electric current stack of elder generation with given module of said wattless current and the given module output of active current; Deduct the transient current in the said three phase mains then, and through modulation ratio M and phase angle
of controller to calculate the required sinusoidal modulation wave of said pulse-width modulation circuit.
Compared with prior art, wind cooling controller of the present invention has following advantage: (1) utilizes the PLC module to replace the conventional means of relay circuit, has avoided loaded down with trivial details wiring and the high defective of relay rate of fault; (2) carry out the control of number of fans according to temperature, can not start fan or a spot of fan lower winter in temperature, temperature just needs to start whole fan heat radiations higher summer, has practiced thrift a large amount of electric energy, has also prolonged the life-span of motor; (3) utilize said chain type SVG control gear, correct, improved the utilization ratio of transformer because machine operation causes the problem of the power factor decline of electrical network; (4) in said chain type SVG control gear, be provided with subsequent use H bridge element circuit; In the time of can a H bridge element circuit breaks down again,, and guarantee H electric bridge multi-type multi-electrical level inverter proper functioning the H bridge element circuit auto by pass of this fault; That is, correct grid power factor; (5) and when this H bridge power model is damaged, need not to shut down maintenance, guaranteed the stable of electrical network; (6) pulse-width modulation circuit is regulated the modulated wave of a phase H bridge power model that is damaged, and has effectively avoided the harmonic wave generation;
(7) independently control the compensation problem that has realized the uneven output of three phase mains through minute phase current.
The technical problem that the present invention also will solve provides a kind of auto by pass fault H bridge element circuit that is suitable for, with the method for work of the chain type SVG control gear that guarantees H electric bridge multi-type multi-electrical level inverter proper functioning.
In order to address the above problem, the present invention also provides a kind of method of work that is suitable for chain type SVG control gear on the basis of said wind cooling controller, comprising:
A: when a H electric bridge element circuit damages, corresponding this H electric bridge element circuit of auto by pass circuit bypass;
B: said pulse-width modulation circuit is on the sampling period basis of invariable that keeps said sample circuit; Change the carrier frequency of said carrier wave pyramidal wave phase shift SPWM of a phase H bridge power model at the H electric bridge element circuit place of said damage, to obtain and this Sampling waveform of corresponding carrier wave pyramidal wave of remaining H electric bridge element circuit quantity phase shift SPWM in H bridge power model mutually;
The method of work of said minute phase current independent controling circuit comprises the steps:
(1) through phaselocked loop according to the momentary value of voltage of the said three phase mains of input to follow the tracks of the voltage-phase of said three phase mains;
(2) voltage-phase that draws according to said phaselocked loop calculates the cosine amount of this voltage-phase and multiplies each other with a wattless current reference value, to obtain actual wattless current output;
(3) voltage-phase that draws according to said phaselocked loop calculates the sinusoidal quantity of this voltage-phase; Subtract each other simultaneously and, export to obtain actual active current through multiplying each other with said sinusoidal quantity again after the PI control according to the voltage reference value of the average voltage of the dc bus capacitor of said each phase H bridge power model and a direct current lateral capacitance;
(4) be used for the electric current stack of elder generation with given module of said wattless current and the given module output of active current; Deduct the transient current in the said three phase mains then, and through modulation ratio M and phase angle
of controller to calculate the required sinusoidal modulation wave of said pulse-width modulation circuit.
Compared with prior art; The method of work of said chain type SVG control gear of the present invention has following advantage: (1) is through setting up at least one subsequent use H electric bridge element circuit in every phase H bridge power model; When H bridge power model was damaged, the auto by pass malfunctioning module need not to shut down maintenance; (2) pulse-width modulation circuit is regulated the modulated wave of a phase H bridge power model that is damaged, and has effectively avoided the harmonic wave generation; (3) independently control the compensation problem that has realized the uneven output of three phase mains through minute phase current.
Description of drawings
For content of the present invention is more clearly understood, below basis specific embodiment and combine accompanying drawing, the present invention is done further detailed explanation, wherein
Fig. 1 wind cooling controller structured flowchart of the present invention;
Fig. 2 chain type SVG control gear of the present invention structured flowchart;
The circuit structure diagram of the multi-electrical level inverter of Fig. 3 H electric bridge of the present invention multi-type;
The structured flowchart of of the present invention minute phase current independent controling circuit of Fig. 4;
The range upon range of SPWM modulated waveform of Fig. 5 carrier wave pyramidal wave of the present invention homophase individual layer figure;
Pulse before Fig. 6 generation of the present invention H electric bridge unit module breaks down generates sequential;
The pulse of Fig. 7 first kind of fault H electric bridge unit module of the present invention after by bypass generates sequential;
The pulse of Fig. 8 second kind of fault H electric bridge unit module of the present invention after by bypass generates sequential.
Embodiment
Below in conjunction with accompanying drawing and embodiment the present invention is elaborated:
Embodiment 1
As shown in Figure 1, a kind of wind cooling controller comprises: temperature detection sensor, plurality of fans, the PLC module that is suitable for just controlling according to external temperature the fan work of respective numbers that links to each other with said temperature detection sensor.
In temperature higher summer, the heating value of transformer is huge, so when the sensor temperature reached 60 degrees centigrade, all fans were all worked; In temperature lower winter, because ambient temperature is lower, so under the not high situation of the heating value of transformer, the fan of can opening less or not blow in.
As shown in Figure 2, wind cooling controller also comprises: one is suitable for correcting the chain type SVG control gear of power factor, and this chain type SVG control gear is connected in the input end of the three phase mains of said wind cooling controller.
Like Fig. 2, shown in 3, said chain type SVG control gear comprises:
The multi-electrical level inverter of H electric bridge multi-type, it is made up of the three-phase H bridge power model that is connected in said three phase mains, wherein, sets up at least one subsequent use H electric bridge element circuit in every phase H bridge power model;
The auto by pass circuit is located at the output terminal of each H electric bridge element circuit, and when a H electric bridge element circuit is damaged, with this H electric bridge element circuit bypass;
Sample circuit is suitable for gathering the momentary value of the voltage and current of said three phase mains, and this momentary value comprises amplitude, the cycle of voltage and current;
Divide the phase current independent controling circuit, it links to each other with said sample circuit is suitable for calculating according to the momentary value of the voltage and current of said three phase mains modulation ratio M and phase angle
of the required sinusoidal modulation wave of said pulse-width modulation circuit;
Pulse-width modulation circuit; Link to each other with said minute phase current independent controling circuit, be used for the carrier wave pyramidal wave phase shift SPWM that adopts between each H electric bridge element circuit being controlled according to modulation ratio M and phase angle
of said sinusoidal modulation wave; Promptly; After the H electric bridge element circuit bypass that damages; This pulse-width modulation circuit is suitable on the sampling period basis of invariable that keeps said sample circuit; Change the carrier frequency of said carrier wave pyramidal wave phase shift SPWM of a phase H bridge power model at the H electric bridge element circuit place of this damage, to obtain and this Sampling waveform of corresponding carrier wave pyramidal wave of remaining H electric bridge element circuit quantity phase shift SPWM in H bridge power model mutually.
See Fig. 4, said minute phase current independent controling circuit comprises:
Phaselocked loop, according to the momentary value of the voltage of said three phase mains to follow the tracks of the voltage-phase of said three phase mains;
The given module of wattless current is suitable for calculating the cosine amount of this voltage-phase and multiplying each other with a wattless current reference value according to the voltage-phase that said phaselocked loop draws, to obtain actual wattless current output;
The given module of active current; Be suitable for calculating the sinusoidal quantity of this voltage-phase according to the voltage-phase that said phaselocked loop draws; Subtract each other simultaneously and, export to obtain actual active current through multiplying each other with said sinusoidal quantity again after the PI control according to the voltage reference value of the average voltage of the dc bus capacitor of said each phase H bridge power model and a direct current lateral capacitance;
The transient current tracking module; Be used for the electric current stack of elder generation with given module of said wattless current and the given module output of active current; Deduct the transient current in the said three phase mains then, and through modulation ratio M and phase angle
of controller to calculate the required sinusoidal modulation wave of said pulse-width modulation circuit.
Wherein reference current is the offset current of expectation, and the VDC reference value is the offset voltage of expectation.
Said pulse-width modulation circuit relates to SPWM PWM method; This SPWM PWM method is to do modulated wave with a sine wave; Doubly do carrier wave with F and carry out waveform relatively and the one group of amplitude that produces equates to the pyramidal wave of sinusoidal modulation wave frequency; Width is proportional to the rectangular pulse train of sinusoidal modulation wave and comes equivalent sine wave, thus the break-make of control switch device (being the switching device in the multi-electrical level inverter).
The present invention adopts the mixing control algorithm of carrier wave pyramidal wave phase shift SPWM control and the stacked SPWM control of carrier wave pyramidal wave: as a whole; Adopt carrier wave pyramidal wave phase shift SPWM control between each H electric bridge element circuit; And single H electric bridge element circuit adopts the method for stacked SPWM control, this modulator approach, and output harmonic wave content is little; Switching frequency is low, and can solve the low problem of inversion efficiency well.
Carrier wave pyramidal wave phase shift SPWM controls method; Be meant for N H electric bridge element circuit; Adopt N phase place different, but frequency carrier wave pyramidal wave and the same sinusoidal modulation wave identical with amplitude compare, produce N and organize SPWM control impuls waveform and remove to control N H bridge respectively; Make each H electric bridge element circuit all export the identical SPWM voltage waveform of fundamental voltage, and then the SPWM voltage waveform of this N H electric bridge element circuit output is superposeed and synthesizes SPWM voltage with multiple levels waveform.
The first phase parallactic angle of N carrier wave pyramidal wave should be removed an angle successively; If adopt bipolarity carrier wave pyramidal wave, this angle is
; If unipolarity carrier wave pyramidal wave, angle are
.
The stacked SPWM control of carrier wave pyramidal wave method is to use the SPWM modulation method of a kind of multi-electrical level inverter relatively early.The stacked SPWM modulation method of carrier wave pyramidal wave can be divided into two kinds, i.e. stacked SPWM modulation method of individual layer and multilayer laminated formula SPWM modulation method, and these two kinds of methods can both reach the technique effect of this patent.
The stacked SPWM modulation method of carrier wave pyramidal wave individual layer can be divided into range upon range of SPWM modulation method of carrier wave pyramidal wave anti-phase individual layer (phase place of two carrier wave pyramidal waves is opposite) and the range upon range of SPWM modulation method of carrier wave pyramidal wave homophase individual layer (phase place of two carrier wave pyramidal waves is identical) again according to the phase relationship of two triangular carriers.Range upon range of SPWM modulation method of carrier wave pyramidal wave anti-phase individual layer and the range upon range of SPWM modulation method of carrier wave pyramidal wave homophase individual layer this in two modulator approach do not have the branch of what quality, the present invention adopts the range upon range of SPWM modulation method of carrier wave pyramidal wave homophase individual layer.
In the range upon range of SPWM modulation method of carrier wave pyramidal wave homophase individual layer; Two carrier wave pyramidal waves
are identical with the phase place of
, and its work wave is as shown in Figure 5.Wherein
and
is the carrier wave pyramidal wave of the upper and lower layer of transverse axis, and
is sinusoidal modulation wave.Compare with pyramidal wave with sinusoidal wave; Output SPWM pulse can be produced at sinusoidal wave
greater than the part of pyramidal wave, the zero pulse of output voltage can be produced at sinusoidal wave
less than the part of pyramidal wave.Because
and
are homophases; That is to say
with
be asymmetric with the coordinate transverse axis; So through comparison sinusoidal wave and pyramidal wave, the positive half cycle and the negative semiaxis of the output voltage SPWM waveform of generation are inequality.
Appoint and to get a H electric bridge element circuit and study, from the power angle analysis.If
is the output voltage of H electric bridge element circuit;
is phase current;
is the angle of output voltage and phase current; Then the active power of H electric bridge element circuit absorption is:
; It is thus clear that, through change H electric bridge element circuit output voltage size, phase current is big or small and angle between them just can change the active power of H bridge absorption.Because the size and Orientation of phase current
is fixed; So can only change the size and Orientation of H electric bridge element circuit output voltage, promptly correspond to the modulation ratio M and the phase shifting angle
of pulse-width modulation circuit output.
The control strategy of chain type SVG adopts the control structure of layering: the main definite total meritorious and wattless power of upper strata control, lower floor's control mainly is to regulate the reasonable distribution of gaining merit between each H bridge of this phase, guarantees the dc capacitor voltage balance.The method of upper strata of the present invention control adopts divides phase current independently to control; Calculate the modulation ratio and the phase angle of the modulated wave of expectation; With the error quantization of each bridge DC side voltage is that sine function is superimposed upon on the modulated wave of this H electric bridge element circuit; Modulated wave phase place to each H electric bridge element circuit is finely tuned, and regulates the distribution of gaining merit between each H electric bridge element circuit.
There is not coupled relation in the three-phase dc side of chain type SVG, thereby can realize phase-splitting control, and three-phase system is compensated respectively, all reasonable compensation effect can be arranged to balance sysmte and unbalanced system.The control strategy that proposes in the leading portion, the full decoupled control of current status is adopted in the control of its upper strata, and transient response is fast, good stability, but the situation when only having considered three-phase equilibrium during design of Controller is not considered the unbalanced problem of three-phase system.Investigation shows that more or less there be the asymmetric of phase place or amplitude in line voltage to power grid quality, that is to say that in actual conditions three-phase system is unbalanced mostly.
The auto by pass circuit adopts the auto by pass technology, and the auto by pass technology is exactly directly with the bypass of fault power module AC side, thereby realizes separating of malfunctioning module and device.Through outlet side a bypass mechanism is set and realizes auto by pass at each power unit module.
The output terminal that can be employed in each H electric bridge element circuit is provided with a relay, utilize control often open with normally off realize fault H electric bridge element circuit with this mutually H bridge power model separate; Also can adopt rectifier bridge and thyristor, the output terminal of each H electric bridge element circuit is connected to the rectifier bridge that two pairs of diodes are formed, so thyristor is under the forward voltage drop all the time.When supervisory system detects the power model internal fault, block the IGBT pulse immediately, and trigger the thyristor conducting, realize that bypass separates; Perhaps adopt bidirectional thyristor.
After having fault H electric bridge element circuit in a certain phase H bridge power model by bypass; If the pulsing of the sinusoidal modulation signal of pulse-width modulation circuit output transmission during still according to normal operation; And the output of this chain type SVG control system has only N H electric bridge element circuit output voltage stack, and harmonic content will increase.Therefore, for a remaining N non-fault H electric bridge element circuit, modulation strategy need be done corresponding adjustment.
Because the stacked SPWM of carrier wave pyramidal wave just works in single H electric bridge element circuit inside, so the malfunctioning module separation only impacts carrier wave pyramidal wave phase shift SPWM not influence of the stacked SPWM modulation of carrier wave pyramidal wave.So, analyze for ease, only carrier wave pyramidal wave phase shift SPWM is analyzed.If during N+1 H electric bridge element circuit series connection, the carrier frequency of this chain type SVG control system is 1/T
c, the sampling period is T
s, when carrier wave is unipolarity, sampling period T
s=T
c/ [2 (N+1)].Separate back two kinds of adjusting method commonly used for below the H electric bridge element circuit that is out of order.
First method: T
cConstant, T
sChange
In order to simplify analysis, before the selection fault, establishing said multi-electrical level inverter number is n+1=6, then the sampling period T of each phase H bridge power model
s=T
c/ 12, at 0/6T
s, T
s/ 7T
s, 2T
s/ 8T
s, 3T
s/ 9T
s, 4T
s/ 10T
s, 5T
s/ 11T
sMoment sample modulation ripple, and relatively generate the relative trigger pulse, as shown in Figure 6.
If a certain H electric bridge element circuit is because of the separated back (supposing that first H electric bridge element circuit is separated) of breaking down, as modulation strategy not being done corresponding adjustment, the pulse that then remains N non-fault H electric bridge element circuit generates sequential shown in Fig. 7 (a).As can be seen from the figure the sampling interval between H electric bridge element circuit 0 and the H electric bridge element circuit 2 is 2T
sBut the sampling interval between other power H electric bridge element circuit is T
s, this does not obviously meet the basic principle of phase-shifting carrier wave SPWM modulation.The harmonic component in output voltage of SVG device must increase.
If carrier cycle is constant, still be T
c, but with the sampling period at T
cIn readjust.Shown in Fig. 7 (b), because after the fault, the quantity of said multi-electrical level inverter becomes 5, thereby the sampling period after the modulation is T
s'=T
c/ 10.To produce the complete phase-shifting carrier wave output pulse of N=5 like this.
This method is adjusted the switch modulation strategy of this phase phase-shifting carrier wave SPWM through the sampling period that changes fault phase (a phase H bridge power model at the H electric bridge element circuit place of breaking down).Concerning this phase, can play good regulating action.
Second method: T
cChange T
sConstant
When first H electric bridge element circuit breaks down when separated, keep sampling period T
sConstant, adjust carrier wave pyramidal wave cycle of this phase.As shown in Figure 8.
The carrier cycle of adjustment back fault phase is Tc ', keeps the carrier cycle Tc of other non-fault phases constant.Adjusted pulse sequence is shown in Fig. 8 (b): at 0/5Ts, Ts/6Ts, 2Ts/7Ts, 3Ts/8Ts, 4Ts/9Ts constantly, a sample modulation ripple generates the trigger impulse of H bridge power model.Like this, obtained the phase-shifting carrier wave SPWM Sampling waveform of complete N=5.Because the sampling period of fault phase does not change, after fault is separated, still can guarantee the synchronism of three phase circuit sampling before and after malfunctioning module separates.
The method of work of said minute phase current independent controling circuit.Figure 4, Figure
,
,
, for the acquisition circuit to phase voltage instantaneous value;
,
,
for the PLL to track the three-phase power supply voltage phase;?
,
,
, as each phase reactive current reference value;
,
,
is each phase H-bridge power modules DC side capacitor voltage averages;
DC side capacitor voltage reference value;
,
,
for the acquisition circuit to the three-phase current instantaneous value; through the corresponding PI controller can calculate the output voltage of the reference signal SVG and further theoretical calculations based on instantaneous reactive corresponding to each phase reactive current reference value and the DC side capacitor voltage reference value.The concrete grammar of the voltage reference value of each phase wattless current reference value of above-mentioned acquisition and dc bus capacitor sees document for details: Yang Jun; Wang Zhaoan, Qiu Guanyuan. the humorous a kind of detecting method [J] that involves wattless current of single-phase circuit, electrotechnics journal; 1996 (3), 11 (3): 42-46; Jiang Bin, Yan Gangfeng, Zhao Guangzhou. the instantaneous humorous real time sampling idle new method [J] that involves of single-phase circuit. power system automation, 2000 (11): 36-39.
See Fig. 2-4, on embodiment 1 basis, the method for work of the chain type SVG control gear that is provided with at the three phase mains place of said air cooler control system comprises:
A: when a H electric bridge element circuit damages, corresponding this H electric bridge element circuit of auto by pass circuit bypass;
B: said pulse-width modulation circuit is on the sampling period basis of invariable that keeps said sample circuit; Change the carrier frequency of said carrier wave pyramidal wave phase shift SPWM of a phase H bridge power model at the H electric bridge element circuit place of said damage, to obtain and this Sampling waveform of corresponding carrier wave pyramidal wave of remaining H electric bridge element circuit quantity phase shift SPWM in H bridge power model mutually;
The method of work of said minute phase current independent controling circuit comprises the steps:
(1) through phaselocked loop according to the momentary value of voltage of the said three phase mains of input to follow the tracks of the voltage-phase of said three phase mains;
(2) voltage-phase that draws according to said phaselocked loop calculates the cosine amount of this voltage-phase and multiplies each other with a wattless current reference value, to obtain actual wattless current output;
(3) voltage-phase that draws according to said phaselocked loop calculates the sinusoidal quantity of this voltage-phase; Subtract each other simultaneously and, export to obtain actual active current through multiplying each other with said sinusoidal quantity again after the PI control according to the voltage reference value of the average voltage of the dc bus capacitor of said each phase H bridge power model and a direct current lateral capacitance;
(4) be used for the electric current stack of elder generation with given module of said wattless current and the given module output of active current; Deduct the transient current in the said three phase mains then, and through modulation ratio M and phase angle
of controller to calculate the required sinusoidal modulation wave of said pulse-width modulation circuit.
Obviously, the foregoing description only be for clearly the present invention is described and is done for example, and be not to be qualification to mode of execution of the present invention.For the those of ordinary skill in affiliated field, on the basis of above-mentioned explanation, can also make other multi-form variation or change.Here need not also can't give exhaustive to all mode of executions.And these belong to conspicuous variation or the change that spirit of the present invention extended out and still are among protection scope of the present invention.
Claims (5)
1. wind cooling controller is characterized in that comprising: temperature detection sensor, plurality of fans, the PLC module that is suitable for just controlling according to external temperature the fan work of respective numbers that links to each other with said temperature detection sensor.
2. wind cooling controller according to claim 1 is characterized in that also comprising: one is suitable for correcting the chain type SVG control gear of power factor, and this chain type SVG control gear is connected in the input end of the three phase mains of said wind cooling controller.
3. wind cooling controller according to claim 2 is characterized in that, said chain type SVG control gear comprises:
The multi-electrical level inverter of H electric bridge multi-type, it is made up of the three-phase H bridge power model that is connected in said three phase mains, wherein, sets up at least one subsequent use H electric bridge element circuit in every phase H bridge power model;
The auto by pass circuit is located at the output terminal of each H electric bridge element circuit, and when a H electric bridge element circuit is damaged, with this H electric bridge element circuit bypass;
Sample circuit is suitable for gathering the momentary value of the voltage and current of said three phase mains;
Divide the phase current independent controling circuit, it links to each other with said sample circuit is suitable for calculating according to the momentary value of the voltage and current of said three phase mains modulation ratio M and phase angle
of the required sinusoidal modulation wave of said pulse-width modulation circuit;
Pulse-width modulation circuit; Link to each other with said minute phase current independent controling circuit, be used for the carrier wave pyramidal wave phase shift SPWM that adopts between each H electric bridge element circuit being controlled according to modulation ratio M and phase angle
of said sinusoidal modulation wave; Promptly; After the H electric bridge element circuit bypass that damages; This pulse-width modulation circuit is suitable on the sampling period basis of invariable that keeps said sample circuit; Change the carrier frequency of said carrier wave pyramidal wave phase shift SPWM of a phase H bridge power model at the H electric bridge element circuit place of this damage, to obtain and this Sampling waveform of corresponding carrier wave pyramidal wave of remaining H electric bridge element circuit quantity phase shift SPWM in H bridge power model mutually.
4. wind cooling controller according to claim 3 is characterized in that, said minute phase current independent controling circuit comprises:
Phaselocked loop, according to the momentary value of the voltage of said three phase mains to follow the tracks of the voltage-phase of said three phase mains;
The given module of wattless current is suitable for calculating the cosine amount of this voltage-phase and multiplying each other with a wattless current reference value according to the voltage-phase that said phaselocked loop draws, to obtain actual wattless current output;
The given module of active current; Be suitable for calculating the sinusoidal quantity of this voltage-phase according to the voltage-phase that said phaselocked loop draws; Subtract each other simultaneously and, export to obtain actual active current through multiplying each other with said sinusoidal quantity again after the PI control according to the voltage reference value of the average voltage of the dc bus capacitor of said each phase H bridge power model and a direct current lateral capacitance;
The transient current tracking module; Be used for the electric current stack of elder generation with given module of said wattless current and the given module output of active current; Deduct the transient current in the said three phase mains then, and through modulation ratio M and phase angle
of controller to calculate the required sinusoidal modulation wave of said pulse-width modulation circuit.
5. the method for work of wind cooling controller according to claim 4 comprises:
The method of work of said chain type SVG control gear comprises the steps:
A: when a H electric bridge element circuit damages, corresponding this H electric bridge element circuit of auto by pass circuit bypass;
B: said pulse-width modulation circuit is on the sampling period basis of invariable that keeps said sample circuit; Change the carrier frequency of said carrier wave pyramidal wave phase shift SPWM of a phase H bridge power model at the H electric bridge element circuit place of said damage, to obtain and this Sampling waveform of corresponding carrier wave pyramidal wave of remaining H electric bridge element circuit quantity phase shift SPWM in H bridge power model mutually;
The method of work of said minute phase current independent controling circuit comprises the steps:
(1) through phaselocked loop according to the momentary value of voltage of the said three phase mains of input to follow the tracks of the voltage-phase of said three phase mains;
(2) voltage-phase that draws according to said phaselocked loop calculates the cosine amount of this voltage-phase and multiplies each other with a wattless current reference value, to obtain actual wattless current output;
(3) voltage-phase that draws according to said phaselocked loop calculates the sinusoidal quantity of this voltage-phase; Subtract each other simultaneously and, export to obtain actual active current through multiplying each other with said sinusoidal quantity again after the PI control according to the voltage reference value of the average voltage of the dc bus capacitor of said each phase H bridge power model and a direct current lateral capacitance;
(4) be used for the electric current stack of elder generation with given module of said wattless current and the given module output of active current; Deduct the transient current in the said three phase mains then, and through modulation ratio M and phase angle
of controller to calculate the required sinusoidal modulation wave of said pulse-width modulation circuit.
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| CN109769404A (en) * | 2016-08-16 | 2019-05-17 | 东芝三菱电机产业系统株式会社 | System interconnection inverter device and its method of operation |
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| CN104505844B (en) * | 2015-01-08 | 2017-01-11 | 国网上海市电力公司 | Cascaded STATCOM capacitor voltage balance control method based on active voltage vector reduplication |
| CN109769404A (en) * | 2016-08-16 | 2019-05-17 | 东芝三菱电机产业系统株式会社 | System interconnection inverter device and its method of operation |
| CN109769404B (en) * | 2016-08-16 | 2021-02-26 | 东芝三菱电机产业系统株式会社 | System interconnection inverter device and method for operating the same |
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