CN102570988A - Amplifier device - Google Patents
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- CN102570988A CN102570988A CN2010106210382A CN201010621038A CN102570988A CN 102570988 A CN102570988 A CN 102570988A CN 2010106210382 A CN2010106210382 A CN 2010106210382A CN 201010621038 A CN201010621038 A CN 201010621038A CN 102570988 A CN102570988 A CN 102570988A
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Abstract
The invention discloses an amplifier device which comprises a gain stage, an output stage, at least one phase compensation circuit and at least one coupling straining element, wherein the gain stage is provided with at least a feedback node; the output stage is coupled to the gain stage and is provided with an output node for outputting an output voltage; each phase compensation circuit is respectively coupled between a corresponding feedback node in the at least one feedback node of the gain stage and the output node; each coupling straining element is respectively coupled between a corresponding feedback node in the at least one feedback node of the gain stage and an individual coupling node, and used for responding to the voltage level change of the corresponding feedback node and then carrying out automatic conduction so as to strain the voltage level change of the corresponding feedback node when the corresponding feedback node is coupled by noises.
Description
Technical field
The invention relates to a kind of amplifier installation, and particularly about a kind of amplifier installation that suppresses the noise coupling.
Background technology
In the operating process of traditional amplifier; Outside noise usually can be coupled to other part of inside of amplifier from output through one or more inner inner phase compensating circuit of amplifier, the result causes non-expection phenomenons such as unusual electric leakage, unusual output waveform, abnormal operation.
Please with reference to Figure 1A, it illustrates the circuit diagram of the traditional amplifier in the example, and it for example can be applicable to sampling and keeps the source electrode driver in (sample-and-hold) circuit or the LCD.If the voltage of load end changes (being so-called outside noise); This outside noise can get into home loop through the output Out that output switch S 1 is coupled to amplifier installation 100 from load end Out; Through inner phase compensating circuit 102 or 104 and further be coupled to other part of inside of amplifier installation 100, the result causes the phenomenon of the unusual electric leakage or the unusual waveforms at load end Out place again.
Please with reference to Figure 1B, it is the signal sequential chart of the amplifier installation 100 of Figure 1A, is the above-mentioned anomaly that how to cause amplifier installation 100 in order to the interprets external noise.After the input voltage vin of amplifier installation 100 is changeed high potential by electronegative potential; Switch S 1 meeting first temporarily disconnected (OFF); The inside of amplifier installation 100 can reach locking through the high potential that input signal is followed in the loop circuit; Therefore the voltage of output end vo ut rises, and the voltage Out of load end then cuts off because of switch S 1 and is maintained electronegative potential.
Next, switch S 1 can transfer conducting (changeing ON by OFF) to, so the electric charge of electric charge on the output end vo ut and load end Out can redistribute.This causes level of output voltage V out past drop-down, and and then causes the feedback node N1 of amplifier installation 100 inner phase compensating circuits 102 and 104 and the current potential of N2 also to be coupled toward drop-down.So transistor M14 closes, and transistor M15 electrorheological is big and transistor M16 electric current diminishes.As a result, the current potential of output voltage V out can be replied and retracted, and load end Out is continued charging.
Yet when amplifier installation 100 continued load end Out charge, (noise) was coupled and but takes place thereupon and cause anomaly for the second time.Specifically, along with load end Out continues to rise because of the charging current potential, the voltage of node N1 and N2 can up be drawn (shown in the left-hand broken line zone of Figure 1B) by coupling for the second time, and then causes transistor M12 to close.So transistor M16 electric current can increase, that is the situation of the outer electric leakage of the direct current amount of flow through transistor M15 and M16.As a result, the waveform of load voltage Out but glides between charge period unusually, so charging rate is slack-off.Shown in Figure 1B, in Vin be high potential during, the true waveform (solid line) of output voltage V out and load voltage Out has anomaly with respect to ideal waveform (dotted line).
Likewise; When input voltage vin is changeed electronegative potential and switch S 1 conducting (changeing ON by OFF) by high potential after; 100 pairs of load end Out discharges of amplifier installation also can cause the noise coupling; Make the voltage of node N1 and node N2 by toward drop-down (shown in the right side dashed region of Figure 1B), and then cause transistor M10 to close.So transistor M15 electric current increases, that is the situation of the outer electric leakage of the direct current amount of flow through transistor M15 and M16.As a result, the waveform of load voltage Out is in but abnormal ascending of interdischarge interval, so the velocity of discharge is slack-off.Shown in Figure 1B, in Vin be electronegative potential during, the true waveform (solid line) of output voltage V out and load voltage Out also has anomaly with respect to ideal waveform (dotted line).
Except above-mentioned because input voltage changes and load end discharges and recharges the outside noise that is caused; Other is any from external disturbance noises such as environment; Also possibly be coupled to the feedback node N1 or the N2 of amplifier, and then cause the anomaly of circuit operation through output Out and phase compensating circuit 102 or 104.
Comprehensively above-mentioned; Tradition amplifier regular meeting causes the operation of other part of internal circuit to be interfered because of outside large-signal or noise are coupled to phase compensating circuit, thereby takes place that output waveform is unusual, operating current leakage current occurs and circuit operation is unusual ... Deng being not the problem of being desired.
Summary of the invention
The purpose of this invention is to provide a kind of amplifier installation, it has the mechanism that suppresses outside noise coupling, therefore can avoid problems such as outside noise caused in the prior art output waveform and operating current be unusual.
According to the present invention a kind of amplifier installation is provided, it is characterized in that, comprising: a gain stage, it has at least one feedback node; One output stage is coupled to this gain stage, and has an output node in order to export an output voltage; At least one phase compensating circuit, central each be coupled to respectively between the corresponding person and this output node in the middle of this at least one feedback node of this gain stage; And at least one coupling suppression element; Each is coupled to respectively between the central corresponding person of this at least one feedback node of this gain stage and the other switching node in the middle of it; Be used to that this correspondence feedback node receives noise coupling and voltage level when changing; The conducting automatically in response to the voltage level change of this correspondence feedback node is to suppress the voltage level change of this correspondence feedback node.
Under preferable situation, this switching node may be selected to be the arbitrary and close node of DC potential this feedback node of amplifier installation built-in potential.
Useful technique effect of the present invention is: when the amplifier installation normal running, the coupling suppression element can not conducting not influence normal running.Yet when amplifier installation has noise to be coupled to phase compensating circuit and when causing its feedback node current potential to change, the coupling suppression element promptly can conducting suppresses the change in voltage of feedback node with the electric current that affords redress.As a result, can effectively avoid the generation of the unusual and leakage current situation of the output waveform of available circuit, thereby effectively improve the quality of output signal.
For there is better understanding above-mentioned and other aspect of the present invention, hereinafter is special lifts preferred embodiment, and conjunction with figs. elaborates as follows:
Description of drawings
Figure 1A illustrates the circuit diagram of a traditional amplifier.
Figure 1B illustrates the signal timing diagram of the amplifier circuit of Figure 1A.
Fig. 2 A illustrates square framework and the thin portion circuit diagram according to the amplifier installation of first embodiment.
Fig. 2 B illustrates the circuit structure diagram of other different embodiment of first and second coupling suppression element among Fig. 2 A.
It is the circuit structure diagram of transistor unit that Fig. 2 C illustrates among Fig. 2 A first and second coupling suppression element.
Fig. 2 D illustrates among Fig. 2 A first and couples suppression element and the second coupling suppression element is the circuit structure diagram of operational amplifier.
Fig. 3 illustrates square framework and the thin portion circuit diagram according to the amplifier installation of second embodiment.
Fig. 4 illustrates square framework and the thin portion circuit diagram according to the amplifier installation of the 3rd embodiment.
Embodiment
First embodiment
Please with reference to Fig. 2 A, it illustrates the square Organization Chart according to the amplifier installation 200 of an embodiment.Shown in Fig. 2 A; Amplifier installation 200 comprises an input stage 20; It is used to receive a differential input voltage Vin, a gain stage 22, and it is coupled to input stage 20, is used for the output of input stage 20 is amplified; And an output stage 24, be used for producing an output voltage V out according to the output of gain stage 20.In addition, output node Vout can be coupled to a load elements 240 through a switch element S1.In this example, an input node of input stage 20 is coupled to output node Vout, and makes amplifier installation 200 form a unity gain buffer (Unit Gain Buffer) or voltage follower (Voltage follower).
In addition, amplifier installation 200 also comprises first phase compensating circuit 206 and second phase compensating circuit 208, and wherein first phase compensating circuit 206 is coupled between the output node Vout of the first feedback node N1 and output stage 24 of gain stage 22.Similarly, 208 of second phase compensating circuits can be coupled between the output node Vout of the second feedback node N2 and output stage 24 of this gain stage 22.
In addition, amplifier installation 200 can also comprise the first coupling suppression element 210 and the second coupling suppression element 212.The first coupling suppression element 210 (directly or indirectly) is coupled between the first feedback node N1 and the one first switching node N5.Similarly, the second coupling suppression element 212 (directly or indirectly) is coupled between the second feedback node N2 and the one second switching node N6.In other words, compare amplifier installation 200 extra first and second coupling suppression elements 210 and 212 that increased with traditional amplifier installation 100 of Figure 1A.
The first coupling suppression element 210 and the second coupling suppression element 212 in order to suppressing through the noise that first and second phase compensating circuit 210 is coupled to first and second feedback node N1 and N2 with 212 from output node Vout, reach the problem of the unusual leakage current of generation to avoid output waveform respectively unusually.For example, this type noise takes place in can be during output voltage V out switching levels.
When output node Vout has noise to take place and is coupled to the first feedback node N1 and when causing the level of the first feedback node N1 to descend; The first coupling suppression element 210 can begin conducting in response to this level changes; And form a charge path and the offset current that circulates comes the first feedback node N1 is charged; Use the level that draws and lifts the first feedback node N1, therefore can suppress this noise.
Similarly; When output node Vout has noise to take place and is coupled to the second feedback node N2 and when causing the level rising of the first feedback node N2; The second coupling suppression element 212 can begin conducting in response to this level changes; And form a discharge path and the offset current that circulates comes the second feedback node N2 is discharged, and using the level that drags down the second feedback node N2, therefore can suppress this noise.
In a preferred embodiment; For the setting up of suppression element 210 and 210 of avoiding being coupled influences the normal operation of amplifier installation 200, can design the conducting of coupling suppression element 210 and 210 or close by its cross-pressure (that is the cross-pressure between feedback node N1/N2 and the switching node N5/N6) and control.Particularly, when the cross-pressure between feedback node N1/N2 and the switching node N5/N6 was lower than a set voltage, coupling suppression element 210/212 was for closing, and can not have influence on the voltage level of feedback node N1/N2.After the level that must wait until feedback node N1/N2 changed to cross-pressure between feedback node N1/N2 and the switching node N5/N6 and is greater than or equal to a set voltage, coupling suppression element 210/212 just began conducting to carry out its inhibit feature that is coupled.
For reaching aforesaid operations, for example can select the position of the first switching node N5 to be positioned at the close node of DC potential of the DC potential and the first feedback node N1, and the DC potential of the second switching node N6 then the DC potential with the second feedback node N2 is close.Thus, under the normal operation that no noise takes place, the cross-pressure between feedback node N1/N2 and the switching node N5/N6 is no more than this set voltage (even almost can equal zero), and the suppression element 210/212 that therefore is coupled is closed.And be coupled to feedback node N1/N2 at noise, and cause cross-pressure between feedback node N1/N2 and the switching node N5/N6 with after being increased to set voltage, coupling suppression element 210/212 just begins conducting to carry out its noise inhibitory action.
Please continue the A with reference to Fig. 2, the thin portion circuit diagram that it also illustrates according to the amplifier installation 200 of first embodiment is used for further explaining the noise inhibit feature of first and second coupling suppression element 210 and 212.It should be noted that this thin portion circuit diagram only makes the usefulness of example explanation, have all different thin portion circuit all can adopt at least one coupling suppression element to implement similar noise coupling and suppress mechanism.
Shown in Fig. 2 A, output stage 24 can comprise the first output switch 202 and the second output switch 204, is in series in output node Vout place.The first output switch 202 can comprise the first output transistor M15; It for example is a P-type mos (P-type metal oxide semiconductor; PMOS) transistor; The second output switch 204 can comprise the second output transistor M16, and it for example is a N type metal oxide semiconductor (N-typemetal oxide semiconductor, a NMOS) transistor.The drain electrode of the first output transistor M15 can be coupled to output node Vout, and source electrode can be coupled to the first operating voltage Vdd; The drain electrode of the second output transistor M16 can couple output node Vout equally, and source electrode then can be coupled to second operating voltage (such as ground connection GND).
Four, the 5th, and the 6th switch 220,222 and 224 for example can comprise the 4th transistor M12, the 5th transistor M14 and the 6th transistor M11 respectively, and these transistors for example are all N type metal oxide semiconductor transistor.The drain electrode of the 4th transistor M12 (node N4) can be coupled to the grid of the second output transistor M16, and source electrode couples the second feedback node N2.The drain electrode of the 5th transistor M14 can be coupled to the second feedback node N2, and source electrode can be coupled to the second operating voltage GND.The drain electrode of the 6th transistor M11 (node N8) can be coupled to the grid of the 5th transistor M14, and grid can couple the grid of the 4th transistor M12.
In addition, first and second coupling suppression element 210 and 212 then all can be embodied as PN diode D4 and D5 in this embodiment.The negative pole end B1 of PN diode D4 can be coupled to the first feedback node N1, and positive terminal B2 then can be coupled to the source electrode (the first switching node N5) of the 3rd transistor M9.The positive terminal H1 of PN diode D5 is coupled to the second feedback node N2, and negative pole end then is coupled to the source electrode (the second switching node N6) of transistor M11.
Below will explain the operation principles of first and second be coupled suppression element 210 and 212 under above-mentioned configuration.When amplifier installation 200 normal runnings; Because the relation of circuit symmetrical; The level of the voltage Vn5 of the voltage Vn1 of the first feedback node N1 and the first switching node N5 is quite approaching; Therefore the voltage of diode D4 poor (=Vn5-Vn1) less than conducting voltage Vt (for example 0.7V), make not conducting of diode D4.Similarly; Because the relation of circuit symmetrical; The level of the voltage Vn6 of the voltage Vn2 of the second feedback node N2 and the second switching node N6 is also quite approaching; Therefore the voltage of diode D5 poor (=Vn2-Vn6) also less than conducting voltage (for example 0.7V), make the 212 not conductings of the second coupling suppression element.As a result, when dc response, coupling suppression element 210 and 212 neither conductings and can not have influence on the normal running of amplifier installation 200.
In the transition period that input voltage vin is changeed high potential by electronegative potential, switch element S1 transfers conducting state to from dissengaged positions, and output voltage V out also transfers high potential to from electronegative potential.The instantaneous level variation meeting of output voltage V out is coupled to the second feedback node N2 through second phase compensating circuit 208, makes that the voltage (being Vn2) of the second feedback node N2 is up drawn.When the voltage Vn6 difference between the two of the voltage Vn2 of the second feedback node N2 and the second switching node N6 during greater than the conducting voltage Vt of PN diode D5, PN diode D5 will be switched on to produce an offset current.This offset current helps to quicken the discharge response of the N2 of second feedback node, that is the voltage that can suppress the second feedback joint N2 rises.As a result, transistor M12 can the prior art that kind shown in Figure 1A not be closed, so the unusual condition shown in Figure 1B can not take place output voltage V out.
Similarly, in the transition period that input voltage vin is changeed electronegative potential by high potential, switch element S1 transfers conducting state to from dissengaged positions, and output voltage V out also transfers electronegative potential to from high potential.The instantaneous level variation meeting of output voltage V out is coupled to the first feedback node N1 through first phase compensating circuit 206, and the voltage (being Vn1) that makes the feedback node N1 that wins is by past drop-down.When the voltage Vn5 difference between the two of the voltage Vn1 of the first feedback node N1 and the first switching node N5 during greater than the conducting voltage Vt of PN diode D6, PN diode D6 will be switched on to produce an offset current.This offset current helps to quicken the charging response of the N1 of first feedback node, and the voltage that therefore can suppress the second feedback joint N2 descends.As a result, transistor M10 can the prior art that kind shown in Figure 1A not be closed, so the unusual condition shown in Figure 1B can not take place output voltage V out.
All be embodied as single diode D4 and D5 respectively though it should be noted that in above-mentioned explanation first and second coupling suppression element 210 and 212, however this explanation only do example explain with and do not make the usefulness of restriction.For example, in other embodiment, first and second coupling suppression element 210 and 212 can also be various electronic components or its combination of other number, connected mode.
For example, first and second coupling suppression element 210 and 212 all can comprise a plurality of PN diodes that are in series respectively.In addition, first and second coupling suppression element 210 and 212 also can comprise the transistor that is connected into the diode pattern that one or more is in series respectively, and it is that so-called diode couples transistor (diode-connectedtransistor).The transistor that is adopted can be field-effect transistor, is metal oxide semiconductcor field effect transistor (Metal-Oxide-Semiconductor Field-Effect Transistor for example; MOSFET) or metal-semiconductor field effect transistor (Metal-Semiconductor Field-Effect Transistor; MESFET), its grid and source/drain join (conducting voltage=critical voltage), also can be junction transistor, are two-carrier junction transistor (BipolarJunction Transistor for example; BJT) ... Or the like.
In addition, when adopting transistor unit, can also be other connected mode for first and second coupling suppression element 210 and 212.Shown in Fig. 2 C, the first coupling suppression element 210 for example is a nmos pass transistor Q1, and it has one source pole and is coupled to the first feedback node N1, and a grid is coupled to the first switching node N5, and drain electrode can couple the first operating voltage Vdd.Similarly, the second coupling suppression element 212 for example is a PMOS transistor Q2, and it has one source pole and couples the second feedback node N2, and a grid is coupled to the second switching node N6, and a drain electrode can be coupled to the second operating voltage GND.When the voltage difference of the source electrode (H1) of the voltage difference of the grid (B2) of transistor Q1 and source electrode (B1) or transistor Q2 and grid (H2) during greater than a critical voltage value, transistor Q1 or Q2 promptly are switched on.In addition, MOS transistor also can be replaced by the transistor of other type, for example is the junction transistor like the class of BJT ... Or the like.
In another alternate embodiment again, first and second coupling suppression element 210 and 212 also can be a kind of operational amplifier.Shown in Fig. 2 B, the first coupling suppression element 210 for example is an operational amplifier OP1, and it has first input end and is coupled to the first feedback node N1, and second input is coupled to the first switching node N5, and has an output (OU1) and be coupled to first input end.Similarly, the second coupling suppression element 212 for example is an operational amplifier OP2, and it has first input end and is coupled to second feedback node N2 end, and second input is coupled to the second switching node N6, and has an output (OU2) and be coupled to first input end.
Comprehensively above-mentioned; As long as not conducting when the amplifier installation normal running and do not influence the normal operation of amplifier installation; And when noise coupling causes the voltage of first and second feedback node N1 and N2 to change automatically conducting suppress the change in voltage of the first feedback node N1 and the second feedback node N2 with the generation offset current; To reach the various electronic components or the device of the function of avoiding output abnormality and leakage current generation, all can be used to be embodied as first and second coupling suppression element 210 and 212.
It should be noted that first and second switching node among first embodiment is to explain with node N5 and N6, yet the present invention is not limited thereto.In other embodiment, each all may be selected to be the close node of DC potential of inner other the arbitrary DC potential of amplifier installation and this feedback node in the middle of first and second switching node.Below will further utilize second embodiment that this point is described.
Second embodiment
Please with reference to Fig. 3, it illustrates square framework and thin portion circuit diagram according to the amplifier installation of second embodiment of the invention.As shown in Figure 3, the difference of the amplifier installation 300 of second embodiment and the amplifier installation 200 of first embodiment is that first and second switching node changes the N7 end (being the drain electrode of transistor M9) of the 3rd switch 218 and the N8 end (being the drain electrode of transistor M11) of the 6th switch 224 respectively into.
In this configuration down, when amplifier installation 300 normal runnings during in dc response, first and second coupling suppression element 310 and 312 cross-pressure be still less than its conducting voltage, so not conducting and do not influence normal running equally.Otherwise, changeing electronegative potential by high potential or change in the transition period of high potential in input voltage vin by electronegative potential, the first or second coupling suppression element 310 suppresses the change in voltage of the first or second switching node N1 or N2 with 312 same meeting conductings.
Likewise; Though in this embodiment; First and second coupling suppression element 310 and 312 is to illustrate to diode D6 and D7 to illustrate; Yet in other embodiment, first and second coupling suppression element 310 and 312 also can comprise a plurality of diode in series, or one or more various types of transistor unit that connects with diode mode or alternate manner or also can be operational amplifier respectively.Remaining circuit structure is all similar with amplifier installation 200 with operation, therefore repeats no more.
The 3rd embodiment
Please with reference to Fig. 4, it illustrates square framework and thin portion circuit diagram according to the amplifier installation of third embodiment of the invention.As shown in Figure 4; The main difference of the amplifier installation 400 of the 3rd embodiment and the amplifier installation 200 of first embodiment is that first switching node is to change an outside direct voltage node (being B2) that is coupled to one first direct voltage Vc1 into, and second switching node then changes an outside direct voltage node (being H2) that is coupled to one second direct voltage Vc2 into.All the other details are all similar with amplifier installation 200, therefore do not give unnecessary details at this.
Once stated as preceding; In order not influence the normal running of amplifier installation 400; The level of the first direct voltage Vc1 can be designed to the absolute difference of direct voltage of itself and the first feedback node N1 less than the conducting voltage of the first coupling suppression element 410, the level of the second direct voltage Vc2 can be designed to its with the absolute difference of the direct voltage of the second feedback node N2 less than second be coupled suppression element 420 conducting voltage.
Likewise; Though in this embodiment; First and second coupling suppression element 410 and 412 is to illustrate to diode D8 and D9 to illustrate; Yet in other embodiment, first and second coupling suppression element 410 and 412 also can comprise a plurality of diode in series, or one or more various types of transistor unit that connects with diode mode or alternate manner or also can be operational amplifier respectively.Remaining circuit structure is all similar with amplifier installation 200 with operation, therefore repeats no more.
It should be noted that; Though in the foregoing description, all be coupled to a feedback node of phase compensating circuit with an end of coupling suppression element; And the other end is coupled to the switching node close with the direct current level of this feedback node (it for example can be intrinsic node or another direct voltage node of inside circuit) and explains for example, yet the present invention is not exceeded with these embodiment.As long as the coupling voltage level that suppression element coupled allows that the coupling suppression element does not influence normal running when amplifier installation operates in dc response; And when noise is coupled to feedback node through phase compensating circuit; Can suppress the variation of this feedback node current potential in response to the current potential change of switching node, neither disengaging technical scope of the present invention.
More than comprehensive, when the amplifier installation normal running, the coupling suppression element can not conducting not influence normal running.Yet when amplifier installation has noise to be coupled to phase compensating circuit and when causing its feedback node current potential to change, the coupling suppression element promptly can conducting suppresses the change in voltage of feedback node with the electric current that affords redress.As a result, the foregoing description can effectively be avoided the generation of the unusual and leakage current situation of the output waveform of available circuit, thereby effectively improves the quality of output signal.
Though the present invention discloses as above with preferred embodiment, yet it is not in order to limit the present invention.Have common knowledge the knowledgeable in the technical field under the present invention, do not breaking away from the spirit and scope of the present invention, when making various changes that are equal to or replacement.Therefore, protection scope of the present invention is when looking accompanying being as the criterion that the application's claim scope defined.
Claims (16)
1. an amplifier installation is characterized in that, comprising:
One gain stage, it has at least one feedback node;
One output stage is coupled to this gain stage, and has an output node in order to export an output voltage;
At least one phase compensating circuit, central each be coupled to respectively between the corresponding person and this output node in the middle of this at least one feedback node of this gain stage; And
At least one coupling suppression element; Each is coupled to respectively between the central corresponding person of this at least one feedback node of this gain stage and the other switching node in the middle of it; Be used to that this correspondence feedback node receives noise coupling and voltage level when changing; The conducting automatically in response to the voltage level change of this correspondence feedback node is to suppress the voltage level change of this correspondence feedback node.
2. amplifier installation according to claim 1 is characterized in that, this noise is coupled to this correspondence feedback node from this output node through this phase compensating circuit.
3. amplifier installation according to claim 1 is characterized in that, also comprises an input stage, and it has a plurality of input nodes, and one are coupled to this output node in the middle of these input nodes.
4. amplifier installation according to claim 1 is characterized in that, this noise is during the switching levels of this output voltage, to take place.
5. amplifier installation according to claim 1 is characterized in that, if the voltage difference between this correspondence feedback node and this indivedual switching nodes is more than or equal to a set voltage, and this coupling suppression element conducting is cut off otherwise be somebody's turn to do the coupling suppression element.
6. amplifier installation according to claim 1; It is characterized in that; When the level of this correspondence feedback node be increased to make this coupling suppression element conducting after, this coupling suppression element forms a discharge path and the offset current that circulates discharges to this correspondence feedback node.
7. amplifier installation according to claim 1; It is characterized in that; When the level of this correspondence feedback node drop to make this coupling suppression element conducting after, this coupling suppression element forms a charge path and the offset current that circulates charges to this correspondence feedback node.
8. amplifier installation according to claim 1 is characterized in that the DC voltage level of these indivedual switching nodes equals the DC voltage level of this correspondence feedback node.
9. amplifier installation according to claim 1 is characterized in that, in the middle of this at least one coupling suppression element this indivedual switching nodes of each be an inner intrinsic node and an outside direct voltage node of this amplifier installation central one.
10. amplifier installation according to claim 1; It is characterized in that; Each comprises one or more diode element that is in series, one or more transistor that is in series in the middle of this at least one coupling suppression element, and in the middle of the operational amplifier at least one.
11. amplifier installation according to claim 1 is characterized in that, this output stage also comprises one first output switch, couple this output node, and this gain stage comprises also:
One first switch comprises:
One first end, couple this first output switch a control end;
One second end couples this correspondence feedback node;
One second switch comprises:
One first end is coupled to this second end of this first switch; And
One second end is coupled to one first operating voltage; And
One the 3rd switch comprises:
One first end is coupled to a control end of this second switch; And
One control end couples a control end of this first switch.
12. amplifier installation according to claim 11 is characterized in that, these indivedual switching nodes couple one in the middle of this first end and one second end of the 3rd switch.
13. amplifier installation according to claim 11; It is characterized in that; This first output switch is a P-type mos transistor, and the negative pole of this diode element couples this correspondence feedback node, and the positive pole of this diode element couples this indivedual switching nodes.
14. amplifier installation according to claim 11; It is characterized in that; This first output switch is a N type metal oxide semiconductor transistor, and the positive pole of this diode element couples this correspondence feedback node, and the negative pole of this diode element couples this indivedual switching nodes.
15. amplifier installation according to claim 11; It is characterized in that this coupling suppression element comprises a transistor unit, this transistor unit has one first end and couples this correspondence feedback node; One control end couples this indivedual switching nodes, and one second end is coupled to an operating voltage.
16. amplifier installation according to claim 1; It is characterized in that; This coupling suppression element comprises an operational amplifier; This operational amplifier has a first input end and couples this correspondence feedback node, and one second input couples this indivedual switching nodes, and an output is coupled to this first input end.
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| CN103441735A (en) * | 2013-05-31 | 2013-12-11 | 华为技术有限公司 | Balance amplifying system and antenna system |
| CN106464219A (en) * | 2014-05-01 | 2017-02-22 | 德克萨斯仪器股份有限公司 | Current-limiting in an amplifier system |
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| US20060066400A1 (en) * | 2004-09-24 | 2006-03-30 | Kang Jae-Sung | Differential amplifier with cascode control |
| CN1588805A (en) * | 2004-10-15 | 2005-03-02 | 威盛电子股份有限公司 | Switch operation amplifier and its acting method |
| CN101504558A (en) * | 2008-02-06 | 2009-08-12 | 联发科技股份有限公司 | Semiconductor circuits capable of mitigating unwanted effects caused by input signal variations |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103441735A (en) * | 2013-05-31 | 2013-12-11 | 华为技术有限公司 | Balance amplifying system and antenna system |
| CN103441735B (en) * | 2013-05-31 | 2016-08-03 | 华为技术有限公司 | Balance amplification system and antenna system |
| CN106464219A (en) * | 2014-05-01 | 2017-02-22 | 德克萨斯仪器股份有限公司 | Current-limiting in an amplifier system |
| CN106464219B (en) * | 2014-05-01 | 2019-07-02 | 德克萨斯仪器股份有限公司 | Current limit in amplifier system |
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| CN102570988B (en) | 2014-12-10 |
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