CN102545563A - Power factor correction (PFC) conversion control method for low output voltage ripple and device thereof - Google Patents
Power factor correction (PFC) conversion control method for low output voltage ripple and device thereof Download PDFInfo
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Abstract
The invention discloses a power factor correction (PFC) conversion control method for low output voltage ripple and a device thereof. After a single-phase PFC controller is used for sampling the input voltage, inductive current and output voltage of a single-phase PFC converter, a control signal of the PFC convertor is obtained through a PFC control strategy; and a controller of a single-phase inverter is used for sampling the input voltage and load current of the single-phase PFC converter to obtain a control target signal of the single-phase converter and sampling the alternating-current output voltage of the converter simultaneously, and ripple same-amplitude phase reversion is realized for the alternating-current output voltage of the converter and the direct-current output voltage of the PFC converter by using an inverter double closed-loop control strategy. Due to the adoption of the method and the device, a high power factor is realized, the output power frequency ripple voltage of the single-phase PFC converter is eliminated simultaneously, the dynamic response of a system is improved, and the problems of low efficiency and high cost of the conventional twos-stage PFC converter are solved. The device can be also applied to low-ripple high-PFC AC/DC (Alternating Current/Direct Current) constant current source design.
Description
Technical field
The present invention relates to electric control appliance, especially auxiliary pfc converter method of work and the device thereof of realizing the low output voltage ripple of DC-AC.
Background technology
In recent years, power electronic technology develops rapidly, becomes the focus of application and research gradually as the power technology of field of power electronics important component part.Switching Power Supply has been established its dominant position in field of power supplies so that its efficient is high, power density is high; But can there be a fatal weakness in it when inserting electrical network through rectifier: power factor lower (generally being merely 0.45～0.75), and in electrical network, can produce a large amount of current harmonicss and reactive power and pollute electrical network.The method that suppresses Switching Power Supply generation harmonic wave mainly contains two kinds: the one, and passive means promptly adopts passive filtering or active filter circuit to come bypass or harmonic carcellation; The 2nd, active method promptly designs high-performance rectifier of new generation, it have input current for sinusoidal wave, harmonic content is low and characteristics such as power factor height, promptly has power factor emendation function.Switch power supply power factor is proofreaied and correct the emphasis of research, mainly is the research of circuit of power factor correction topology and the exploitation of Power Factor Correction Control integrated circuit.Multiple circuit of power factor correction topological structures such as existing Buck, Boost, Buck-Boost.The Power Factor Correction Control integrated circuit is responsible for detecting the operating state of converter, and produces pulse signal control switch device, regulates the energy that passes to load and exports with stable; The input current that guarantees Switching Power Supply is simultaneously followed the tracks of the electrical network input voltage, realizes approaching 1 power factor.The control method decision that the structure of control integrated circuit and operation principle are adopted by Switching Power Supply.For same power circuit topology, adopt the Different control method to exert an influence to aspects such as the stable state accuracy of Switching Power Supply and dynamic properties.
Traditional active power factor correcting converter VD includes two times of power frequency ripples; If two times of power frequency output voltage ripples are introduced in the power factor correction controller; Can make the input current of power factor correcting converter contain the triple harmonic current composition, reduce the input power factor of power factor correcting converter.So the VD feedback control loop cut-off frequency of traditional APFC converter is low, and (generally be merely 10～20Hz), this has a strong impact on the dynamic response capability of power factor correcting converter to load variations.In addition; Because the VD ripple of APFC converter is bigger; Need after the very big output capacitance of capacitance of power factor correcting converter output termination; Need connect again also that a DC-DC converter improves the stable state accuracy of load VD and to the dynamic response capability of load variations, make that the converter design cost is high, efficient is low.
Summary of the invention
The purpose of this invention is to provide the auxiliary pfc converter method of work that realizes the low output voltage ripple of a kind of DC-AC; Adopt this method that Single-phase PFC converter output voltage ripple is reduced; And its dynamic response performance is good; Efficient is high, and antijamming capability is strong, is applicable to the Single-phase PFC converter of various topological structures.
The present invention realizes its goal of the invention, and the technical scheme that is adopted is: a kind of method of work of Switching Power Supply, and its concrete practice is:
The upper end of the last termination load of single-phase power factor correcting converter direct current output capacitance; The lower end of single-phase power factor correcting converter direct current output capacitance connects the upper end that single-phase inverter exchanges output capacitance; Single-phase inverter exchanges the lower end of the following termination load of output capacitance, the lower end ground connection of load simultaneously.Inductive current, input voltage and the load VD of single-phase power factor correcting controller sampling single-phase power factor correcting converter, process existing P FC control strategy (multiplier control strategy, Cycle Control strategy etc.) obtains the control signal of power factor correcting converter.The input voltage of the controller sampling single-phase power factor correcting converter of single-phase inverter and the controlled target signal that load current obtains single-phase inverter; Sample the simultaneously ac output voltage of inverter of the controller of single-phase inverter makes the same amplitude of VD ripple, the antiphase of the ac output voltage and the power factor correcting converter of inverter through inverter control strategies such as two closed-loop controls.
The operation principle of each controller is following: input voltage detection circuit VC
1Detect the rectification input voltage V of Single-phase PFC converter TD
In, input voltage effective value testing circuit VC
2Detect the rectification input voltage effective value V of Single-phase PFC converter TD
Rms, output voltage detecting circuit VC
3Detect the VD V of load R
o, inductive current detection circuit IC
1Detect the inductive current I of Single-phase PFC converter TD
LVD V
oWith DC reference voltage V
DC-refDifference multiply by rectification input voltage V again after through the PI controller compensation
InAs an input of divider, another of divider is input as rectification input voltage effective value V
RmsSquare, the output of divider is benchmark sinusoidal current I
RefInductive current I
LWith benchmark sinusoidal current I
RefDifference send into PWM generator after through the PI controller compensation, obtain the control impuls of Single-phase PFC converter TD.Input voltage detection circuit VC
4Detect the AC-input voltage V of Single-phase PFC converter TD
In_AC, output current detection circuit IC
2Detect the electric current I of load R
o, AC-input voltage V
In_ACThrough after the frequency multiplier circuit DU frequency multiplication with load current I
oThe control reference voltage V that multiplies each other and obtain single-phase inverter IN
AC-refAc output voltage testing circuit VC
5Detect the ac output voltage V of single-phase inverter IN
O_AC, ac output voltage V
O_ACWith control reference voltage V
C-refDifference send into PWM generator after through the PI controller compensation, obtain the control impuls of single-phase inverter IN.
Compared with prior art, the invention has the beneficial effects as follows:
1, with respect to existing power factor correcting converter, when adopting power factor correcting converter of the present invention to be in stable state, reduced the VD ripple of load effectively, help the converter current rectifying and wave filtering circuit and select less output capacitance for use; 2, adopt power factor correcting converter of the present invention can improve the cut-off frequency of output voltage feedback control loop, so load is when undergoing mutation, controller can change with reference to sinusoidal current immediately, and converter can get into new stable state rapidly; 3, adopt the power factor correcting converter of inventing to need not the DC-DC converter of back level, only need a low power VD ripple compensation inverter, improved the efficient of converter complete machine.
Another object of the present invention provides a kind of device of realizing above Switching Power Supply method of work.
The present invention realizes that the technical scheme that this goal of the invention adopts is:
A kind of device of realizing above Switching Power Supply method of work is made up of Single-phase PFC converter TD, single-phase inverter IN and controller.The upper end of the last termination load of Single-phase PFC converter direct current output capacitance; The lower end of Single-phase PFC converter direct current output capacitance connects the upper end that single-phase inverter exchanges output capacitance; Single-phase inverter exchanges the lower end of the following termination load of output capacitance, the lower end ground connection of load simultaneously.
Controller comprises voltage detecting circuit VCC, current detection circuit IC, compensating network CN, multiplier MU, divider DV, frequency multiplier circuit DU, logic comparator circuit LC and drive circuit DR.Described output voltage detecting circuit VC
3With compensating network CN
1Link to each other; Input voltage detection circuit VC
1With compensating network CN
1Output respectively with multiplier MU
1Link to each other input voltage effective value testing circuit VC
2With multiplier MU
2Link to each other multiplier MU
1Output and multiplier MU
2Output with link to each other the output of divider DV and inductive current detection circuit IC respectively with divider DV
1Be difference back and compensating network CN
2Link to each other compensating network CN
2Output and logic comparator circuit LC
1After linking to each other again with drive circuit DR
1Link to each other.Described AC-input voltage testing circuit VC
4DU links to each other with frequency multiplier circuit, the output of frequency multiplier circuit DU and load current detection circuit IC
2Respectively with multiplier MU
3Link to each other multiplier MU
3Output and ac output voltage testing circuit VC
5Be difference back and compensating network CN
3Link to each other compensating network CN
3Output and logic comparator circuit LC
2After linking to each other again with drive circuit DR
2Link to each other.
Adopt above device can realize the above method of the present invention easily and reliably.
Below in conjunction with accompanying drawing and embodiment the present invention is done further detailed explanation.
Description of drawings
Fig. 1 is a system architecture diagram of the present invention.
Fig. 2 is the electrical block diagram of the embodiment of the invention one.
Fig. 3 a is the time-domain-simulation oscillogram of the embodiment of the invention one output voltage under limit.
Fig. 3 b is the time-domain-simulation oscillogram of the embodiment of the invention one input voltage under limit.
Fig. 3 c is the time-domain-simulation oscillogram of the embodiment of the invention one input current under limit.
Fig. 3 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, inductance L
2=0.2mH, capacitor C
1=C
2=330uF, load resistance R=160 Ω, single phase boost pfc converter voltage control loop compensating parameter K
p=152, K
I=150, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65, single-phase full-bridge inverter voltage control loop compensating parameter K
p=100, K
I=0.5.
Fig. 4 a is the time-domain-simulation oscillogram of the embodiment of the invention one output voltage under limit.
Fig. 4 b is the time-domain-simulation oscillogram of the embodiment of the invention one input voltage under limit.
Fig. 4 c is the time-domain-simulation oscillogram of the embodiment of the invention one input current under limit.
Fig. 4 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, inductance L
2=0.2mH, capacitor C
1=C
2=330uF, load resistance R=400 Ω, single phase boost pfc converter voltage control loop compensating parameter K
p=152, K
I=150, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65, single-phase full-bridge inverter voltage control loop compensating parameter K
p=100, K
I=0.5.
Fig. 5 a is the time-domain-simulation oscillogram of the low VD feedback control loop cut-off frequency single phase boost pfc converter output voltage under limit of tradition.
Fig. 5 b is the time-domain-simulation oscillogram of the low VD feedback control loop cut-off frequency single phase boost pfc converter input voltage under limit of tradition.
Fig. 5 c is the time-domain-simulation oscillogram of the low VD feedback control loop cut-off frequency single phase boost pfc converter input current under limit of tradition.
Fig. 5 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, capacitor C
1=330uF, load resistance R=160 Ω, single phase boost pfc converter voltage control loop compensating parameter K
p=10.7, K
I=10.6, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65.
Fig. 6 a is the time-domain-simulation oscillogram of the low VD feedback control loop cut-off frequency single phase boost pfc converter output voltage under limit of tradition.
Fig. 6 b is the time-domain-simulation oscillogram of the low VD feedback control loop cut-off frequency single phase boost pfc converter input voltage under limit of tradition.
Fig. 6 c is the time-domain-simulation oscillogram of the low VD feedback control loop cut-off frequency single phase boost pfc converter input current under limit of tradition.
Fig. 6 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, capacitor C
1=330uF, load resistance R=400 Ω, single phase boost pfc converter voltage control loop compensating parameter K
p=10.7, K
I=10.6, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65.
Fig. 7 a is the time-domain-simulation oscillogram of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter output voltage under limit.
Fig. 7 b is the time-domain-simulation oscillogram of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter input voltage under limit.
Fig. 7 c is the time-domain-simulation oscillogram of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter input current under limit.
Fig. 7 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, capacitor C
1=330uF, load resistance R=160 Ω, single phase boost pfc converter voltage control loop compensating parameter K
p=152, K
I=150, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65.
Fig. 8 a is the time-domain-simulation oscillogram of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter output voltage under limit.
Fig. 8 b is the time-domain-simulation oscillogram of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter input voltage under limit.
Fig. 8 c is the time-domain-simulation oscillogram of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter input current under limit.
Fig. 8 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, capacitor C
1=330uF, load resistance R=400 Ω, single phase boost pfc converter voltage control loop compensating parameter K
p=152, K
I=150, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65.
Fig. 9 is the simulation waveform figure of the embodiment of the invention one converter output voltage when load variations (load on 0.5s constantly by 0.4KW transition to 1KW).
Fig. 9 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, inductance L
2=0.2mH, capacitor C
1=C
2=330uF, single phase boost pfc converter voltage control loop compensating parameter K
p=152, K
I=150, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65, single-phase full-bridge inverter voltage control loop compensating parameter K
p=100, K
I=0.5.
Figure 10 is the simulation waveform figure of the embodiment of the invention one converter output voltage when load variations (load on 0.5s constantly by 1KW transition to 0.4KW).Figure 10 simulated conditions is identical with Fig. 9.
Figure 11 is the simulation waveform figure of the low VD feedback control loop cut-off frequency single phase boost pfc converter of tradition converter output voltage when load variations (load on 0.5s constantly by 0.4KW transition to 1KW).
Figure 11 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, capacitor C
1=330uF, single phase boost pfc converter voltage control loop compensating parameter K
p=10.7, K
I=10.6, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65.
Figure 12 is the simulation waveform figure of the low VD feedback control loop cut-off frequency single phase boost pfc converter of tradition converter output voltage when load variations (load on 0.5s constantly by 1KW transition to 0.4KW).Figure 12 simulated conditions is identical with Figure 11.
Figure 13 is the simulation waveform figure of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter converter output voltage when load variations (load on 0.5s constantly by 0.4KW transition to 1KW).
Figure 13 simulated conditions is following: input voltage V
In=220V, VD reference value V
Ref=400V, inductance L
1=1mH, capacitor C
1=330uF, single phase boost pfc converter voltage control loop compensating parameter K
p=152, K
I=150, single phase boost pfc converter current regulator compensating parameter K
p=0.7, K
I=0.65.
Figure 14 is the simulation waveform figure of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter converter output voltage when load variations (load on 0.5s constantly by 1KW transition to 0.4KW).Figure 14 simulated conditions is identical with Figure 13.
Figure 15 is the electrical block diagram of the embodiment of the invention two.
Figure 16 is the electrical block diagram of the embodiment of the invention three.
Embodiment
Embodiment one
Fig. 2 illustrates, and a kind of embodiment of the present invention does, a kind of control method of Switching Power Supply, and its concrete practice is:
Input voltage detection circuit VC
1Detect the rectification input voltage V of single phase boost pfc converter
In, input voltage effective value testing circuit VC
2Detect the rectification input voltage effective value V of single phase boost pfc converter
Rms, output voltage detecting circuit VC
3Detect the VD V of load R
o, inductive current detection circuit IC
1Detect single phase boost pfc converter inductive current I
LVD V
oSend error amplifier VA
1, error amplifier VA
1Use DC reference voltage V
DC-refWith VD V
0Compare and produce error voltage value Δ V
DCError voltage value Δ V
DCThrough compensating network CN
1Regulate and multiply by rectifier output voltage V again
InAs an input of divider, by divider divided by rectification input voltage effective value V
RmsSquare, the output of divider is benchmark sinusoidal current I
RefInductive current I
LSend error amplifier VA
2, error amplifier VA
2With benchmark sinusoidal current I
RefWith inductive current I
LCompare and produce error current value Δ I; Error current value Δ I is through compensating network CN
2Regulate with carrier wave comparing, produce switching tube SW according to comparative result
1Control impuls P
N1, through drive circuit DR
1Switch SW to the single phase boost pfc converter
1The output control signal.Input voltage detection circuit VC
4Detect the AC-input voltage V of single phase boost pfc converter
In_AC, output current detection circuit IC
2Detect the electric current I of load R
o, input voltage detection circuit VC
5Detect the ac output voltage V of single-phase full-bridge inverter
O_ACAc output voltage V
In_ACThrough after the frequency multiplier circuit DU frequency multiplication with load current I
oThe control reference voltage V that multiplies each other and obtain single-phase full-bridge inverter
AC-refAc output voltage V
O_ACSend error amplifier VA
3, error amplifier VA
3With control reference voltage V
AC-refWith ac output voltage V
P_ACCompare to produce and exchange error voltage value Δ V
ACExchange error voltage value Δ V
ACThrough compensating network CN
3Regulate with carrier wave comparing, produce switching tube SW according to comparative result
2～SW
5Control impuls P
N2～P
N5, through drive circuit DR
2Switch SW to single-phase full-bridge inverter
2～SW
5The output control signal.
Fig. 2 illustrates, and a kind of embodiment of the present invention is: the power factor correcting converter of low output voltage ripple.In this example, inductive current, input voltage and the load VD of power factor correction controller sampling single phase boost pfc converter, the traditional two closed loop compensations of process calculate the control signal of power factor correcting converter.The controller of single-phase full-bridge inverter comes controlled reference voltage through the AC-input voltage of detection single phase boost pfc converter and the electric current of load R; Obtain the controlled target signal of single-phase full-bridge inverter through frequency multiplier circuit DU, make the same amplitude of VD ripple, the antiphase of the ac output voltage and the Boost pfc converter of single-phase full-bridge inverter.Load R voltage is the ac output voltage sum of the VD and the single-phase full-bridge inverter of Boost pfc converter, so the VD ripple that the ac output voltage of controller through single-phase full-bridge inverter contains the direct voltage at load R two ends is low.
This routine Single-phase PFC converter is the Boost code converter, and single-phase inverter is the bridge-type inverter.
With Matlab/Simulink software this routine method is carried out the time-domain-simulation analysis, the result is following.
Fig. 3 is the time-domain-simulation analysis result of the 1KW low output voltage ripple single phase boost pfc converter of the embodiment of the invention one, and each component (a) and (b), (c) are respectively output voltage, input voltage and inductive current waveform.Converter input current when stable state is followed the tracks of input voltage, and output voltage waveforms is stabilized in set point 400V, realizes the function of power factor converter.This moment, the output voltage ripple peak-to-peak value was 3.58V; The proportion that input current 3,5,7,9,11,13,15 and 17 subharmonic account for first-harmonic is respectively 6.75%, 2.41%, 0.61%, 0.35%, 0.32%, 0.26%, 0.2% and 0.15%, and total percent harmonic distortion is 7.22%.
Fig. 4 is the analysis result of time-domain-simulation of the 0.4KW low output voltage ripple single phase boost pfc converter of the embodiment of the invention one, and each component (a) and (b), (c) are respectively output voltage, input voltage and inductive current waveform.Converter input current when stable state is followed the tracks of input voltage, and output voltage waveforms is stabilized in set point 400V, realizes the function of power factor converter.This moment, the output voltage ripple peak-to-peak value was 2.14V; The proportion that input current 3,5,7,9,11,13,15 and 17 subharmonic account for first-harmonic is respectively 10.31%, 2.88%, 0.53%, 0.27%, 0.08%, 0.07%, 0.04% and 0.04%, and total percent harmonic distortion is 10.73%.
Fig. 5 is the time-domain-simulation analysis result of the 1KW single phase boost pfc converter of the low VD feedback control loop cut-off frequency of tradition, and each component (a) and (b), (c) are respectively output voltage, input voltage and inductive current waveform.Converter input current when stable state is followed the tracks of input voltage, and output voltage waveforms is stabilized in set point 400V, realizes the function of power factor converter.This moment, the output voltage ripple peak-to-peak value was 25.91V; The proportion that input current 3,5,7,9,11,13,15 and 17 subharmonic account for first-harmonic is respectively 4.07%, 0.4%, 0.33%, 0.28%, 0.23%, 0.17%, 0.12% and 0.07%, and total percent harmonic distortion is 4.13%.
Fig. 6 is the time-domain-simulation analysis result of the 0.4KW single phase boost pfc converter of the low VD feedback control loop cut-off frequency of tradition, and each component (a) and (b), (c) are respectively output voltage, input voltage and inductive current waveform.Converter input current when stable state is followed the tracks of input voltage, and output voltage waveforms is stabilized in set point 400V, realizes the function of power factor converter.This moment, the output voltage ripple peak-to-peak value was 11.15V; The proportion that input current 3,5,7,9,11,13,15 and 17 subharmonic account for first-harmonic is respectively 5.55%, 1.18%, 0.58%, 0.16%, 0.04%, 0.02%, 0.11% and 0.16%, and total percent harmonic distortion is 5.73%.
Fig. 7 is the time-domain-simulation analysis result of the 1KW single phase boost pfc converter of traditional high VD feedback control loop cut-off frequency, and each component (a) and (b), (c) are respectively output voltage, input voltage and inductive current waveform.Converter output voltage waveforms when stable state is stabilized in set point 400V, but there is serious triple-frequency harmonics distortion at this moment in input current, fails to realize the function of power factor converter.This moment, the output voltage ripple peak-to-peak value was 29.22V; The proportion that input current 3,5,7,9,11,13,15 and 17 subharmonic account for first-harmonic is respectively 43.44%, 9.65%, 1.56%, 0.03%, 0.18%, 0.17%, 0.15% and 0.13%, and total percent harmonic distortion is 44.52%.
Fig. 8 is the time-domain-simulation analysis result of the 0.4KW single phase boost pfc converter of traditional high VD feedback control loop cut-off frequency, and each component (a) and (b), (c) are respectively output voltage, input voltage and inductive current waveform.Converter output voltage waveforms when stable state is stabilized in set point 400V, but there is serious triple-frequency harmonics distortion at this moment in input current, fails to realize the function of power factor converter.This moment, the output voltage ripple peak-to-peak value was 12.73V; The proportion that input current 3,5,7,9,11,13,15 and 17 subharmonic account for first-harmonic is respectively 44.58%, 9.95%, 1.26%, 0.26%, 0.39%, 0.32%, 0.25% and 0.21%, and total percent harmonic distortion is 45.70%.
Can find out by Fig. 3～Fig. 8; The output voltage ripple peak-to-peak value was minimum when the embodiment of the invention one worked in stable state at the single phase boost pfc converter; And the input current harmonics aberration rate only is a bit larger tham the single phase boost pfc converter of the low VD feedback control loop cut-off frequency of tradition, is starkly lower than the single phase boost pfc converter of traditional high VD feedback control loop cut-off frequency.
Fig. 9 changes front and back, the output voltage waveforms of the embodiment of the invention one for load becomes 1KW by 0.4KW.In the diagram, load on 0.5s when changing constantly, the single phase boost pfc converter of the embodiment of the invention one can get into new stable state rapidly.The output voltage magnitude is 4.4V, and the output voltage overshoot is 3V, needs the 0.013s system just can get back to stable state (the output voltage fluctuation range of ± 2V).It is thus clear that the embodiment of the invention one has good dynamic characteristic when load increases.
Figure 10 changes front and back, the output voltage waveforms of the embodiment of the invention one for load becomes 0.4KW by 1KW.In the diagram, load on 0.5s when changing constantly, the single phase boost pfc converter of the embodiment of the invention one can get into new stable state.The output voltage magnitude is 0V, and the output voltage overshoot is 7.5V, needs the 0.01s system just can get back to stable state (the output voltage fluctuation range of ± 2V).It is thus clear that the embodiment of the invention one has good dynamic characteristic when load reduces.
Figure 11 changes front and back, the output voltage waveforms of the low VD feedback control loop cut-off frequency single phase boost pfc converter of tradition for load becomes 1KW by 0.4KW.In the diagram, load on 0.5s when changing constantly, it is slow that the low VD feedback control loop cut-off frequency single phase boost pfc converter of tradition gets into new steady state speed.The output voltage magnitude is 42.5V, and the output voltage overshoot is 18.9V, needs the 0.11s system just can get back to stable state (the output voltage fluctuation range of ± 12V).It is thus clear that the low VD feedback control loop cut-off frequency single phase boost pfc converter transient response speed when load increases of tradition is slow, and the magnitude of output voltage and overshoot are big, and stable state accuracy is also low.
Figure 12 changes front and back, the output voltage waveforms of the low VD feedback control loop cut-off frequency single phase boost pfc converter of tradition for load becomes 0.4KW by 1KW.In the diagram, load on 0.5s when changing constantly, it is slow that the low VD feedback control loop cut-off frequency single phase boost pfc converter of tradition gets into new steady state speed.The output voltage magnitude is 40.35V, and the output voltage overshoot is 17.56V, needs the 0.15s system just can get back to stable state (the output voltage fluctuation range of ± 5V).It is thus clear that the low VD feedback control loop cut-off frequency single phase boost pfc converter transient response speed when load reduces of tradition is slow, and the magnitude of output voltage and overshoot are big, and stable state accuracy is also low.
Figure 13 changes front and back, the output voltage waveforms of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter for load becomes 1KW by 0.4KW.In the diagram, load on 0.5s when changing constantly, it is very fast that traditional high VD feedback control loop cut-off frequency single phase boost pfc converter gets into new steady state speed.The output voltage magnitude is 19.5V, and the output voltage overshoot is 14V, needs the 0.017s system just can get back to stable state (the output voltage fluctuation range of ± 10V).It is thus clear that the low VD feedback control loop cut-off frequency single phase boost pfc converter transient response speed when load increases of tradition is very fast, but the magnitude of output voltage and overshoot are big, and stable state accuracy is also low.
Figure 14 changes front and back, the output voltage waveforms of traditional high VD feedback control loop cut-off frequency single phase boost pfc converter for load becomes 0.4KW by 1KW.In the diagram, load on 0.5s when changing constantly, it is very fast that traditional high VD feedback control loop cut-off frequency single phase boost pfc converter gets into new steady state speed.The output voltage magnitude is 6.1V, and the output voltage overshoot is 8.1V, needs the 0.024s system just can get back to stable state (the output voltage fluctuation range of ± 5V).It is thus clear that the low VD feedback control loop cut-off frequency single phase boost pfc converter transient response speed when load reduces of tradition is very fast, but the magnitude of output voltage and overshoot are big, and stable state accuracy is also low.
Can find out by Fig. 9～Figure 14; The embodiment of the invention one works in output voltage ripple minimum under the transient state at converter; Stable state accuracy is the highest; And the magnitude of output voltage and overshoot are all minimum when load increases and reduces, and the adjustment time is also the shortest, obviously are superior to the low VD feedback control loop cut-off frequency single phase boost pfc converter of tradition and traditional high VD feedback control loop cut-off frequency single phase boost pfc converter.
Embodiment two
Figure 15 illustrates; This example is compared with embodiment one; Difference is: the output voltage of sampling single phase boost pfc converter obtains the output voltage ripple of single phase boost pfc converter after straight through block isolating circuit ID, with this control reference signal voltage V as single-phase full-bridge inverter
AC-refThe control mode and the course of work and embodiment one are similar.Can prove that equally it can realize the object of the invention through simulation result.
Embodiment three
Figure 16 illustrates, and this example is compared with embodiment one, and difference is: the pfc converter of Switching Power Supply is an isolated form Boost converter.The control mode and the course of work and embodiment one are similar.Can prove that equally it can realize the object of the invention through simulation result.
The Switching Power Supply that the Boost pfc converter of the inventive method in can be used for above embodiment formed; Also can be used for the PFC Switching Power Supply that multiple power circuit such as Buck converter, Cuk converter, forward converter, anti exciting converter, half-bridge converter, full-bridge converter, non-bridge PFC converter, isolated form pfc converter is formed; Its control strategy place among the above embodiment outside the Average Current Control strategy of Boost pfc converter, other pfc converter control strategies such as also available peak current control, Cycle Control.The full-bridge inverter and univoltage ring control strategy thereof of single-phase inverter in the foregoing description, also inverter control strategy such as inverter topology such as available half-bridge inverter and two closed loops.
Claims (7)
1. the power factor correction conversion control method of a low output voltage ripple adopts the auxiliary pfc converter low output voltage ripple of realizing of DC-AC, it is characterized in that: Single-phase PFC converter TD direct current output capacitance C
1The upper end of last termination load R, Single-phase PFC converter TD direct current output capacitance C
1The lower end meet single-phase inverter IN and exchange output capacitance C
2The upper end, single-phase inverter IN exchanges output capacitance C
2The lower end of following termination load R, the lower end ground connection of the R of load simultaneously; Inductive current, input voltage and the load VD of single-phase power factor correcting controller sampling single-phase power factor correcting converter, process PFC control strategy obtains the control signal of power factor correcting converter; The input voltage of the controller sampling single-phase power factor correcting converter of single-phase inverter and the controlled target signal that load current obtains single-phase inverter; Sample the simultaneously ac output voltage of inverter of the controller of said single-phase inverter makes the same amplitude of VD ripple, the antiphase of the ac output voltage and the power factor correcting converter of inverter through the two closed-loop control strategies of inverter.
2. the power factor correction conversion control method of low output voltage ripple as claimed in claim 1 is characterized in that, the control method of said Single-phase PFC converter TD is:
Input voltage detection circuit VC
1Detect the rectification input voltage V of Single-phase PFC converter TD
In, input voltage effective value testing circuit VC
2Detect the rectification input voltage effective value V of Single-phase PFC converter TD
Rms, output voltage detecting circuit VC
3Detect the VD V of load R
o, inductive current detection circuit IC
1Detect the inductive current I of Single-phase PFC converter TD
LVD V
oWith DC reference voltage V
DC-refDifference multiply by rectification input voltage V again after through the PI controller compensation
InAs an input of divider, another of divider is input as rectification input voltage effective value V
RmsSquare, the output of divider is benchmark sinusoidal current I
RefInductive current I
LWith benchmark sinusoidal current I
RefDifference send into PWM generator after through the PI controller compensation, obtain the control impuls of Single-phase PFC converter TD.
3. the power factor correction conversion control method of low output voltage ripple as claimed in claim 1 is characterized in that, the control method of said single-phase inverter IN is:
Input voltage detection circuit VC
4Detect the AC-input voltage V of Single-phase PFC converter TD
In_AC, output current detection circuit IC
2Detect the electric current I of load R
o, AC-input voltage V
In_ACThrough after the frequency multiplier circuit DU frequency multiplication with load current I
oThe control reference voltage V that multiplies each other and obtain single-phase inverter IN
AC-refAc output voltage testing circuit VC
5Detect the ac output voltage V of single-phase inverter IN
O_AC, ac output voltage V
O_ACWith control reference voltage V
AC-refDifference send into PWM generator after through the PI controller compensation, obtain the control impuls of single-phase inverter IN.
4. the power factor correction conversion control method of low output voltage ripple as claimed in claim 1 is characterized in that, the control method of described single-phase inverter IN is:
Output voltage ripple testing circuit VC
4Detect the VD of Single-phase PFC converter TD, obtain the output voltage ripple of Single-phase PFC converter TD after straight and as the control reference voltage V of single-phase inverter IN through block isolating circuit ID
AC-ref, ac output voltage testing circuit VC
5Detect the ac output voltage V of single-phase inverter IN
O_ACAc output voltage V
O_ACWith control reference voltage V
AC-refDifference send into PWM generator after through the PI controller compensation, obtain the control impuls of single-phase inverter IN.
5. the power factor correction conversion control method of low output voltage ripple as claimed in claim 1 is characterized in that, described PFC control strategy comprises Average Current Control, peak current control, Cycle Control.
6. control device of realizing the power factor correction conversion control method of claim or 1 or 2 or 3 or 4 or 5 described low output voltage ripples; Form by Single-phase PFC converter TD, single-phase inverter IN and controller; It is characterized in that; The upper end of the last termination load of Single-phase PFC converter direct current output capacitance; The lower end of Single-phase PFC converter direct current output capacitance connects the upper end that single-phase inverter exchanges output capacitance, and single-phase inverter exchanges the lower end of the following termination load of output capacitance, the lower end ground connection of load simultaneously.
7. control device as claimed in claim 6, wherein the Single-phase PFC converter topology is common Boost converter, Buck converter, full-bridge converter, anti exciting converter; The single-phase inverter topology is full-bridge, half-bridge or Boost type inverter topology.
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| CN107015167A (en) * | 2016-12-30 | 2017-08-04 | 国网天津市电力公司 | A kind of Switching Power Supply ripple voltage detection method based on detection techniques |
| CN107810593A (en) * | 2015-06-29 | 2018-03-16 | 皇家飞利浦有限公司 | Estimation to the average value of the inductor current of switched mode power converter |
| CN107825973A (en) * | 2017-12-22 | 2018-03-23 | 东南大学 | Novel electric vehicle charging circuit and its control method |
| CN108923638A (en) * | 2018-09-11 | 2018-11-30 | 西南交通大学 | A kind of control method and device of continuous mode boost power factor correcting converter |
| CN109075697A (en) * | 2018-02-11 | 2018-12-21 | 深圳欣锐科技股份有限公司 | The ripple optimal control method and interlock circuit of pfc circuit output voltage |
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| CN107825973A (en) * | 2017-12-22 | 2018-03-23 | 东南大学 | Novel electric vehicle charging circuit and its control method |
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| CN109075697B (en) * | 2018-02-11 | 2020-10-02 | 深圳欣锐科技股份有限公司 | Ripple optimization control method for PFC circuit output voltage and related circuit |
| CN108923638A (en) * | 2018-09-11 | 2018-11-30 | 西南交通大学 | A kind of control method and device of continuous mode boost power factor correcting converter |
| CN108923638B (en) * | 2018-09-11 | 2023-10-27 | 西南交通大学 | Control method and device of continuous mode boost power factor correction converter |
| CN114026441A (en) * | 2019-06-27 | 2022-02-08 | 依必安派特穆尔芬根有限两合公司 | Circuit and method for monitoring a DC bus capacitor |
| CN112653331A (en) * | 2020-12-24 | 2021-04-13 | 漳州科华技术有限责任公司 | Control method of DCDC converter and terminal equipment |
| CN115995955A (en) * | 2023-03-23 | 2023-04-21 | 茂睿芯（深圳）科技有限公司 | Power factor correction converter based on fixed turn-off time and control method thereof |
| CN115995955B (en) * | 2023-03-23 | 2023-06-06 | 茂睿芯（深圳）科技有限公司 | Power factor correction converter based on fixed turn-off time and control method thereof |
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