CN102111932A - Light-emitting diode current balance circuit - Google Patents
Light-emitting diode current balance circuit Download PDFInfo
- Publication number
- CN102111932A CN102111932A CN2009102616873A CN200910261687A CN102111932A CN 102111932 A CN102111932 A CN 102111932A CN 2009102616873 A CN2009102616873 A CN 2009102616873A CN 200910261687 A CN200910261687 A CN 200910261687A CN 102111932 A CN102111932 A CN 102111932A
- Authority
- CN
- China
- Prior art keywords
- resistance
- coupled
- current
- lamp string
- transistor
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Landscapes
- Circuit Arrangement For Electric Light Sources In General (AREA)
Abstract
The invention discloses a light-emitting diode current balance circuit, and belongs to the technical field of light-emitting diode driving. The light-emitting diode current balance circuit comprises a reference current generator, a current mirror and a voltage compensation circuit. The reference current generator provides reference current with a robust power voltage disturbance resistant characteristic for the current mirror to generate absorption current to each lamp string, and a framework used in the current mirror is not influenced by a transistor gain ratio, so the current mirror can stably control the current flowing through each lamp string. The voltage compensation circuit detects the voltage at end points of each lamp string so as to compensate forward conduction voltage drop. Lamp strings with different forward conduction voltage drops can be lightened, and the current flowing through the lamp strings is more balanced. In addition, a special light-emitting diode (LED) controller is not needed, and the light-emitting diode current balance circuit is low in cost and competitive.
Description
Technical field
The present invention relates to the light-emitting diode Driving technique, particularly a kind of led current balancing circuitry.
Background technology
LED (Light-Emitting Diode, light-emitting diode) ideal value that forward conduction voltage drop indicates on specifications is 3.3V, will inevitably there be error in actual forward conduction voltage drop with this ideal value of 3.3V after but LED connected circuit, if there is 5% error, then the forward conduction voltage drop of LED reality may be between 3.135V～3.465V.Therefore, even by the formed lamp string of the LED coupled in series of equal number, same type (light bar), on each lamp string, still can produce different forward conduction voltage drops, if applying identical lamp string on each lamp string presses, each lamp string will make the electric current that flows through each lamp string inequality because of the forward conduction voltage drop of reality cause inequality, and the brightness that provides of each lamp string is also just inequality certainly.For the forward conduction voltage drop that the solves lamp string reality current unevenness problem that flows through that causes inequality, current balance circuit just becomes the important driving element of LED lamp string.
Fig. 1 is a kind of circuit diagram of existing single led lamp string mobile equilibrium circuit.See also Fig. 1, lamp string 11 comprises the light-emitting diode D1～Dn (n is a positive integer) of a plurality of coupled in series, and the forward conduction voltage drop Vf1 of lamp string 11 is the summation of the forward conduction voltage drop of each light-emitting diode D1～Dn.First end of lamp string 11 presses VBUS to obtain the required bias voltage of conducting by the receiving light crosstalk, and second end of lamp string 11 is coupled to current balance circuit.Current balance circuit comprises transistor Q, detect resistance R and operational amplifier OP, wherein, detect resistance R and detect the current value that flows through lamp string 11, the inverting input of operational amplifier OP receives the detection resistance R and detects the current value (its corresponding current actual value) that flows through lamp string 11, non-inverting input receives control command Vset (its corresponding current set point), send the control end of signal according to both differences from output again to transistor Q, change pressure drop on the transistor Q with the working point of adjusting transistor Q, and then the forward conduction voltage drop Vf1 of change lamp string 11, make the current actual value convergence current setting value that flows through lamp string 11.
Fig. 2 is a kind of circuit diagram of existing a plurality of LED lamp string mobile equilibrium circuit.See also Fig. 2, when using a plurality of LED lamp string 11～1m (m is positive integer), second end of each lamp string 1i (i is arbitrary positive integer among 1～m) all needs to be coupled to a current balance circuit as shown in Figure 1, make the current setting value of the current value convergence control command Vset correspondence that flows through each lamp string 1i, and then the current value that flows through each lamp string 1i is equated or in certain error range (promptly reaching current balance type).When the quantity big more (or m is big more) of lamp string 11～1m, the number of needed current balance circuit is also more and more certainly, except increasing cost and circuit area, each current balance circuit also can cause the electric current current-sharing deleterious between each lamp string 1i because of the error that included separately transistor Q, detection resistance R and operational amplifier OP itself exist.
There is the integrated circuit of many moneys special LED controller 22 to be devised in recent years.Led controller 22; for example with a plurality of as shown in Figure 1 the current balance circuit miniaturization and be integrated on the wafer; each current balance circuit is coupled to second end of corresponding lamp string 1i by tunnel ends CHi; usually also can adjust lamp string and press the VBUS value by feedback end FB control DC/DC (Direct Current/Direct Current, dc-dc) transducer 21.Though integrated circuit can reach more accurate control and littler circuit area, but the reliability of integrated circuit is not as traditional circuit, and electric current and the power loss limited (being generally less than 60mA) that can bear because of integrated circuit, in the LED of high-voltage great-current lamp string is used, also need to add transistor and other element on the contrary and come balanced balanced current, for the designer, not only can not save cost, circuit more complicated and be not easy control.
Summary of the invention
The electric current and the circuit that flow through each lamp string for more stable strangulation are controlled simply easily, the invention provides a kind of led current balancing circuitry.Described technical scheme is as follows:
A kind of led current balancing circuitry is used to drive a plurality of lamp strings, and each lamp string includes the light-emitting diode of a plurality of coupled in series, and each lamp string first end all is coupled to a lamp string and presses.This led current balancing circuitry comprises:
One current mirror, a reference current generator and a voltage compensating circuit.Current mirror is used for producing a plurality of current drawn according to a reference current when opening, and each current drawn provides to second end of a corresponding lamp string, make to flow through each lamp string stream and reach balance, and to make the current value that flows through each lamp string when closing is zero.Reference current generator comprises one first bipolar transistor, one adjustable shunt regulator, one first resistance and one second resistance, adjustable shunt regulator has cathode terminal, anode tap and reference edge, the first bipolar transistor collector terminal is coupled to first end of a supply voltage and first resistance, the base terminal of first bipolar transistor is coupled to second end of first resistance and the cathode terminal of adjustable shunt regulator, the emitter terminal of first bipolar transistor is coupled to the reference edge of adjustable shunt regulator and first end of second resistance, the anode tap of adjustable shunt regulator is coupled to a ground connection, second end output reference current of second resistance.Voltage compensating circuit comprises a plurality of first diodes, one second bipolar transistor, one the 3rd resistance to one the 8th resistance and one first electric capacity, the cathode terminal of each first diode is coupled to second end of a corresponding lamp string, the anode tap of each first diode all is coupled to first end of the 3rd resistance and first end of the 4th resistance, second end of the 3rd resistance is coupled to the reference edge of adjustable shunt regulator and first end of the 5th resistance, second end of the 4th resistance and second end of the 5th resistance are coupled to the base terminal and the collector terminal of second bipolar transistor respectively, first end of the 6th resistance and second end are coupled to the emitter terminal and the ground connection of second bipolar transistor respectively, first end of the 7th resistance is coupled to the collector terminal of second bipolar transistor and first end of first electric capacity, second end of the 7th resistance is coupled to first end of the 8th resistance, second end of the 8th resistance is coupled to second end and the ground connection of first electric capacity, first end of the 8th resistance is exported a compensating signal, and compensating signal is used to adjust lamp string pressure value.
Further, current mirror comprises the first transistor and a transistor seconds of a plurality of couplings, each the first transistor and transistor seconds all have first end, second end and control end, first end of each the first transistor is coupled to second end of a corresponding lamp string so that a corresponding current drawn to be provided, second end that first end of transistor seconds is coupled to control end and is coupled to second resistance is to receive reference current, second end of each the first transistor and transistor seconds all is coupled to ground connection, and the control end of each the first transistor and transistor seconds is coupled to each other.
Further, each the first transistor and transistor seconds are bipolar transistor or are field-effect transistor.Further, second end of each the first transistor and transistor seconds all is coupled to ground connection by a corresponding resistance.
Further, current mirror is not opened when the control end of transistor seconds is coupled to ground connection, and closes when the control end of transistor seconds is coupled to ground connection.
Further, the led current balancing circuitry also comprises an over-voltage detection circuit, over-voltage detection circuit is coupled to second end of each lamp string, be used for exporting when second terminal voltage that detects arbitrary lamp string surpasses an overvoltage threshold rub-out signal, it is zero that rub-out signal is used to make lamp string pressure value.
Further, over-voltage detection circuit comprises a plurality of second diodes, one Zener diode, one the 9th resistance, 1 the tenth resistance and one second electric capacity, the anode tap of each second diode is coupled to second end of a corresponding lamp string, the cathode terminal of each second diode all is coupled to the cathode terminal of Zener diode, the anode tap of Zener diode is coupled to first end of the 9th resistance, second end of the 9th resistance is coupled to first end of the tenth resistance and first end of second electric capacity, second end of the tenth resistance is coupled to second end and the ground connection of second electric capacity, the first end output error signal of the tenth resistance.
Further, during less than a constant current threshold value, first bipolar transistor ends at supply voltage value, and the reference current value of reference current generator output determined by supply voltage value, by variable supply voltage as dim signal to realize simulating light modulation.
Further, at supply voltage value during greater than a constant current threshold value, the first bipolar transistor conducting and adjustable shunt regulator operate as normal, the reference current of reference current generator output constant current, the led current balancing circuitry also comprises a light adjusting circuit, light adjusting circuit is coupled to reference current generator and/or current mirror, be used for receiving a pulse-width signal and according to pulse-width signal alternately opening and closing reference current generator and/or current mirror from a light modulation termination, by with the pulse-width signal of pulse width variability as dim signal to realize digital dimming.Here, " reference current generator and/or current mirror " expression " reference current generator ", " current mirror ", " reference current generator and current mirror " three select one.
Further, supply voltage is coupled to the light modulation end instead, in the duty ratio of pulse-width signal during greater than a duty cycle threshold, pulse-width signal level during the high level activation is a constant voltage and greater than the constant current threshold value, and in the duty ratio of pulse-width signal during less than duty cycle threshold, pulse-width signal level during the high level activation is variable and less than the constant current threshold value.
The present invention can provide the reference current with strong anti-supply voltage disturbance characteristic to produce current drawn to each lamp string for current mirror because of the reference current generator that adopts, and the framework that current mirror adopts is not influenced by the transistor gain ratio, therefore current mirror can be stablized the electric current that each lamp string is flow through in strangulation, and add voltage compensating circuit and detect the voltage of each lamp string end points so that the forward conduction voltage drop of each lamp string is compensated, different forward each lamp string of conduction voltage drop all can be lighted except guaranteeing to have, also can make the electric current balance more that flows through each lamp string, and because of not adopting special LED controller and cost quite cheap and have more competitiveness.
Description of drawings
Fig. 1 is the circuit diagram of a kind of single led lamp string mobile equilibrium circuit that provides of prior art;
Fig. 2 is the circuit diagram of a kind of a plurality of LED lamp string mobile equilibrium circuit of providing of prior art;
Fig. 3 is the block diagram of a kind of LED current balance circuit of providing of the embodiment of the invention 1;
Fig. 4 is the circuit diagram of a kind of LED current balance circuit of providing of the embodiment of the invention 1;
Fig. 5 is the component symbol and the functional schematic of the adjustable shunt regulator shown in Figure 4 that provides of the embodiment of the invention 1;
Fig. 6 A is the signal mode graphoid of first kind of LED current balance circuit shown in Figure 4 of providing of the embodiment of the invention 1;
Fig. 6 B is the signal mode graphoid of second kind of LED current balance circuit shown in Figure 4 of providing of the embodiment of the invention 1;
Fig. 7 is the actual signal survey map of the LED current balance circuit shown in Figure 4 that provides of the embodiment of the invention 1.
In the accompanying drawing, the list of parts of each label representative is as follows:
11～1m: the lamp string, the 21:DC/DC transducer, the 22:LED controller,
CH1～CHm: tunnel ends, FB: feedback end, the 31:DC/DC transducer,
32: reference current generator, 33: current mirror, 34: voltage compensating circuit,
35: over-voltage detection circuit, 36: light adjusting circuit, DIM: the light modulation end, C1: first electric capacity,
C2: second electric capacity, D1～Dn: light-emitting diode, D11～D1m: first diode,
D21～D2m: second diode, OP: operational amplifier, Q: transistor,
Q11～Q1m: the first transistor, Q22: transistor seconds, Q1: first bipolar transistor,
Q2: second bipolar transistor, Q3～Q6: transistor switch, R: detect resistance,
R1～R10: first resistance～the tenth resistance, R11～R1m, R22: degeneration resistance,
R31～R34: current-limiting resistance, TL1: adjustable shunt regulator, ZD1: Zener diode,
I1～Im: current drawn, Iref: reference current, VIN: input voltage, VBUS: lamp string is pressed,
VCC, VEE: supply voltage, VREF: reference voltage, Vcomp: compensating signal,
Vf1～Vfm: lamp string conduction voltage drop, Vfault: rub-out signal, Von-off: power switch signal,
Vpwm: pulse-width modulation (PWM) signal, Vset: control command.
Embodiment
For making the purpose, technical solutions and advantages of the present invention clearer, embodiment of the present invention is described further in detail below in conjunction with accompanying drawing.
At first need to prove, those skilled in the art know bipolar transistor (Bipolar JunctionTransistor, abbreviation BJT) has first end (being collector terminal), second end (being emitter terminal) and control end (being base terminal), field-effect transistor (Field-Effect Transistor, abbreviation FET) has first end (being drain electrode end), second end (being source terminal) and control end (being gate terminal), resistance (resistor) and electric capacity (capacitor) all have first end and second end, diode, light-emitting diode and Zener diode (Zener diode) all have anode tap and cathode terminal, below repeat no more.
Fig. 3 and Fig. 4 are respectively the block diagram and the circuit diagram of the LED current balance circuit that the embodiment of the invention provides.Please be simultaneously referring to Fig. 3 and Fig. 4, the LED current balance circuit is used to drive a plurality of lamp string 11～1m, and each lamp string 1i includes the light-emitting diode D1～Dn of a plurality of coupled in series, and wherein m, n are positive integer, and i is arbitrary positive integer among 1～m.Each lamp string 1i all has first end and second end, and first end of each lamp string 1i all presses VBUS to obtain the required bias voltage of conducting by being coupled to lamp string.Those skilled in the art know in order to allow these lamp strings 11～1m be able to operate as normal, in each lamp string 1i, the anode tap of light-emitting diode D1 should be coupled to first end of lamp string 1i, the cathode terminal of light-emitting diode Dk should be coupled to the anode tap of light-emitting diode Dk+1, and the cathode terminal of light-emitting diode Dn should be coupled to second end of lamp string 1i, wherein, k is arbitrary positive integer in 1～(n-1).The led light source that these lamp strings 11～1m forms can be used as Backlight For Liquid Crystal Display Panels, for example straight-down negative or lateral incident type backlight source.
The LED current balance circuit comprises DC/DC transducer 31, reference current generator 32, current mirror 33, voltage compensating circuit 34, over-voltage detection circuit 35 and light adjusting circuit 36.
DC/DC transducer 31 is the buck or boost transducer, is used for power supply unit (Fig. 3 and Fig. 4 all do not draw) is provided the DC input voitage VIN of specifications such as common 5V, 12V or 24V to be converted to the direct current lamp string and presses VBUS to drive lamp string 11～1m.DC/DC transducer 31 also receives power switch signal Von-off, rub-out signal Vfault and compensating signal Vcomp.Wherein, power switch signal Von-off for example can make DC/DC transducer 31 be used to produce lamp string when high level and press VBUS supply lamp string 11～1m and produce supply voltage VCC supply LED current balance circuit internal circuit, and DC/DC transducer 31 is no longer powered.
Reference current generator 32 comprises the first bipolar transistor Q1, adjustable shunt regulator (programmable shunt regulator) TL1, first resistance R 1 and second resistance R 2.Wherein, the TL431 that the integrated circuit of modal adjustable shunt regulator TL1 has Texas Instruments to produce, its component symbol has cathode terminal, anode tap and reference edge shown in the left figure of Fig. 5, and its functional schematic is shown in the right figure of Fig. 5.Can see from the right figure of Fig. 5, adjustable shunt regulator TL1 inside has a constant pressure source provides the reference voltage VREF of fixed value 2.5V inverting input to operational amplifier OP, the non-inverting input of operational amplifier OP is coupled to reference edge, only at reference voltage terminal during very near reference voltage VREF, transistor Q just has a stable unsaturation electric current and flows through, and along with the minor variations of reference voltage terminal, the electric current that flows through transistor Q will change at 1A～100mA.
In reference current generator 32, the collector terminal of the first bipolar transistor Q1 is coupled to first end of the DC power supply voltage VCC and first resistance R 1, the base terminal of the first bipolar transistor Q1 is coupled to second end of first resistance R 1 and the cathode terminal of adjustable shunt regulator TL1, the emitter terminal of the first bipolar transistor Q1 is coupled to the reference edge of adjustable shunt regulator TL1 and first end of second resistance R 2, the anode tap of adjustable shunt regulator TL1 is coupled to ground connection, second end output reference current Iref of second resistance R 2.
In supply voltage VCC value during greater than the constant current threshold value, the first bipolar transistor Q1 conducting and adjustable shunt regulator TL1 operate as normal, adjustable shunt regulator TL1 is almost constant voltage and can be used as the DC power supply voltage VEE that voltage compensating circuit 34 is given in power supply at the voltage of reference edge (or first end of second resistance R 2), so reference current generator 32 also can be provided with reference current Iref value by the resistance value that second resistance R 2 is set by supply voltage VCC power supply.After the resistance value of second resistance R 2 was determined, reference current Iref value also was confirmed as constant current, so the voltage (or second terminal voltage of second resistance R 2) of reference current generator 32 outputs also is confirmed as constant voltage.The constant voltage of reference current generator 32, the output of constant current can make current mirror 33 more stably work.If adjustable shunt regulator TL1 is an example with integrated circuit TL431, collector terminal is to the about 1V of emitter terminal pressure drop during the first bipolar transistor Q1 conducting, and the voltage of the reference edge of adjustable shunt regulator TL1 is about 2.5V, so the constant current threshold value is about 3.5V.In addition, supply voltage VCC value must have a upper limit, and electric current and power loss that this upper limit can be born during mainly by the first bipolar transistor Q1 conducting are determined.
In the present embodiment, current mirror 33 comprises the first transistor Q11～Q1m and the transistor seconds Q22 of a plurality of couplings, and each the first transistor Q1i and transistor seconds Q22 are the NPN bipolar transistor and have first end (being collector terminal), second end (being emitter terminal) and control end (being base terminal); But be not limited only to this, for example each the first transistor Q1i and transistor seconds Q22 also can be the N channel fet and have first end (being drain electrode end), second end (being source terminal) and control end (being gate terminal).First end of each the first transistor Q1i is coupled to second end of corresponding lamp string 1i so that corresponding current drawn Ii to be provided, first end that first end of transistor seconds Q22 is coupled to control end and connects into diode transistors (diode-connectedtransistor) and transistor seconds Q22 also is coupled to second end of second resistance R 2 of reference current generator 32 to receive reference current Iref, second end of each the first transistor Q1i and transistor seconds Q22 all is coupled to ground connection, and the control end of each the first transistor Q1i and transistor seconds Q22 is coupled to each other.The cause that current mirror 33 mates owing to the first transistor Q11～Q1m when opening, current drawn I1～Im the value that flows into the first transistor Q11～Q1m equates or in error range necessarily (promptly reaching current balance type), force the electric current that flows through each lamp string 1i to reach balance equally, make lamp string 11～1m that uniform brightness is provided.
In the present embodiment, second end of each the first transistor Q1i also is coupled to ground connection by corresponding resistance R 1i, second end of transistor seconds Q22 also is coupled to ground connection by corresponding resistance R 22, current drawn I1～Im that resistance R 11～R1m can make the first transistor Q11～Q1m produce is not influenced than unmatched by transistor gain, so resistance R 11～R1m is called as degeneration resistance (degeneration resistor).In addition, be coupled to ground connection, transistor seconds Q22 and each the first transistor Q1i are all ended, reach the purpose of close current mirror 33 by control end with transistor seconds Q22; Be not coupled to ground connection and work as transistor seconds Q22 control end, make transistor seconds Q22 and the equal operate as normal of each the first transistor Q1i, reach the purpose of firing current mirror 33.
Suppose that each lamp string 1i includes 13 light-emitting diode D1～D13, ideally lamp string 1i forward conduction voltage drop be 42.9V, and suppose this moment the first transistor Q1i of current mirror 33 and the pressure drop of resistance R 1i be 1V, so ideally lamp string presses VBUS to should be 43.9V and lamp string second terminal voltage should be 1V.But, in fact each lamp string 11～1m has forward conduction voltage drop of difference, exist part lamp string (as lamp string 11) to be slightly larger than 42.9V, also exist part lamp string (as lamp string 12) to be slightly less than 42.9V, this moment is in order all can to light each lamp string 11～1m, the lamp string pressure VBUS that applies when lighting a lamp must be slightly larger than 43.9V is lighted lamp string 11, but but cause second terminal voltage of lamp string 12 too high like this, make in the current mirror 33 corresponding the first transistor Q11 and resistance R 11 pressure drops too high, be under the current balance type at lamp string 11～1m, the first transistor Q11 in the current mirror 33 and resistance R 11 can produce more power losss and shorten useful life, but so the embodiment of the invention adjust by voltage compensating circuit 34 that lamp strings are pressed VBUS values so that in the power loss of guaranteeing the equal ignition condition decline low current mirror 33 of each lamp string.
Because ideally second terminal voltage of lamp string is 1V, and suppose the first diode D1i forward conduction voltage drop be 0.7V, therefore ideally the anode tap voltage of the first diode D1i is 1.7V, when the anode tap voltage of the first diode D1i during greater than 1.7V, the second bipolar transistor Q2 conducting, force the voltage that is stored on the capacitor C 1 to descend, the pressure drop of capacitor C 1 by resistance R 7 and R8 dividing potential drop with output compensating signal Vcomp; When the anode tap voltage of the first diode D1i during less than 1.7V, the second bipolar transistor Q2 ends, supply voltage VEE directly by resistance R 5, R7 and R8 dividing potential drop with output compensating signal Vcomp.Ideally compensating signal Vcomp magnitude of voltage is about 1V, and when compensating signal Vcomp magnitude of voltage during less than 1V, DC/DC transducer 31 is turned down the lamp string of output and pressed the VBUS value; When compensating signal Vcomp magnitude of voltage during greater than 1V, DC/DC transducer 31 is heightened the lamp string of output and is pressed the VBUS value.Because supply voltage VCC value is greater than the constant current threshold value, supply voltage VEE is a constant voltage, suppose the second bipolar transistor Q2 conducting, this moment, the anode tap voltage of the first diode D1i was (VEE-Vbe2) * [R4+ (1+ β) * R6]/[R3+R4+ (1+ β) * R6], wherein, base terminal was to the emitter terminal pressure drop when Vbe2 was the second bipolar transistor Q2 conducting, and β is the second bipolar transistor Q2 cascode current gain.Therefore, the anode tap voltage of the first diode D1i can be set by the resistance value that resistance R 3, R4 and R6 are set, for example greater than 1.7V the time, make the second bipolar transistor Q2 conducting, and the second bipolar transistor Q2 is ended.
Over-voltage detection circuit 35 is coupled to second end of each lamp string 1i, is used for output error signal Vault when second terminal voltage that detects arbitrary lamp string surpasses overvoltage threshold, and it is zero that rub-out signal Vault is used to make lamp string to press the VBUS value.
In the present embodiment, over-voltage detection circuit 35 comprises a plurality of second diode D21～D2m, Zener diode ZD1, the 9th resistance R 9, the tenth resistance R 10 and second capacitor C 2.The anode tap of each second diode D2i is coupled to second end of corresponding lamp string 1i, the cathode terminal of each second diode D2i all is coupled to the cathode terminal of Zener diode ZD1, the anode tap of Zener diode ZD1 is coupled to first end of the 9th resistance R 9, second end of the 9th resistance R 9 is coupled to first end of the tenth resistance R 10 and first end of second capacitor C 2, second end of the tenth resistance R 10 is coupled to second end and the ground connection of second capacitor C 2, the first end output error signal Vfault of the tenth resistance R 10.When second terminal voltage of arbitrary lamp string (as lamp string 11) among lamp string 11～1m makes Zener diode ZD1 collapse above overvoltage threshold, second terminal voltage of lamp string 11 deduct diode D21 forward the pressure drop behind pressure drop and the Zener diode ZD1 breakdown voltage will drop on the 9th resistance R 9 and the tenth resistance R 10, setting make the tenth resistance R 10 minutes voltage (i.e. first terminal voltage of the tenth resistance R 10) be high level, can represent output error signal Vfault.When second terminal voltage of arbitrary lamp string among lamp string 11～1m can't not make Zener diode ZD1 collapse above overvoltage threshold, to there be drop of pressure in the 9th resistance R 9 and the tenth resistance R 10, the tenth resistance R 10 minutes voltage be zero or low level, can represent not output error signal Vfault.In addition, can design different overvoltage thresholds, ability output error signal Vfault when what light-emitting diodes tube short circuits are arranged in the lamp string promptly is set by the Zener diode that uses different breakdown voltages.
In supply voltage VCC value during greater than the constant current threshold value, the reference current Iref of reference current generator 32 output constant currents, make that current mirror 33 is constant current according to current drawn I1～Im that reference current Iref produces, therefore will force the electric current that flows through lamp string 11～1m when current mirror 33 is opened is constant current, be that lamp string 11～1m provides changeless brightness, need this moment to adopt digital dimming to realize adjusting the function of led light source brightness.Digital dimming promptly is by opening and closing current mirror 33 alternately, make lamp string 11～1m alternately luminous (bright) not luminous (secretly) once once, if bright dark switching frequency is more than 100Hz, human eye will be because of the imperceptible bright dark variation of the influence of the persistence of vision, can only feel the mean value of this variation, promptly human eye can only be experienced mean flow rate and this mean flow rate is directly proportional with bright dark ratio.Therefore,, and then adjust the bright dark ratio of lamp string 11～1m, can realize adjusting the function of led light source brightness in the digital dimming mode by the time scale of adjustment current mirror 33 opening and closing.
In the present embodiment, by light adjusting circuit 36 opening and closing current mirror 33 alternately.Light adjusting circuit 36 is coupled to reference current generator 32 and/or current mirror 33, receive PWM (Pulse-Width Modulation from light modulation end DIM, pulse-width modulation) signal Vpwm, and according to pwm signal Vpwm alternately opening and closing reference current generator 32 and/or current mirror 33, and adjust the time scale of current mirror 33 opening and closing by the pulsewidth (or duty ratio) of adjusting pwm signal Vpwm.Therefore, promptly be pwm signal Vpwm by pulse width variability as dim signal input light adjusting circuit 36, with by light adjusting circuit 36 alternately opening and closing current mirror 33 realize the digital dimming function.
In the present embodiment, light adjusting circuit 36 comprises transistor switch Q3～Q6 and current-limiting resistance R31～R34.When pwm signal Vpwm was low level, transistor switch Q5 ended, the Q6 conducting, and the transistor Q11～Q1m of current mirror 33 and Q22 base terminal all are coupled to ground connection and end, and no longer produce current drawn I11～I1m, and expression current mirror 33 is closed.When pwm signal Vpwm was high level, transistor switch Q5 conducting, Q6 ended, and light adjusting circuit 36 does not influence the running of current mirror 33, and expression current mirror 33 is unlocked.In addition, when power switch signal Von-off is low level, transistor switch Q3 ends, the Q4 conducting, the base terminal of the first bipolar transistor Q1 of reference current generator 32 is coupled to ground connection and ends, and the cathode terminal of adjustable shunt regulator TL1 and anode tap all are coupled to ground connection and make reference current Iref and supply voltage VEE be zero, and expression reference current generator 32 is closed.When power switch signal Von-off was high level, transistor switch Q3 conducting, Q4 ended, and light adjusting circuit 36 does not influence the running of reference current generator 32, and expression reference current generator 32 is unlocked.
Fig. 6 A and Fig. 6 B are the signal mode graphoid of LED current balance circuit shown in Figure 4, and wherein to drive 6 lamp strings 11～16 and the electric current I 1～I6 that flows through lamp string 11～16 is set be 20mA to the LED current balance circuit.Please earlier referring to Fig. 6 A, be under 50% the condition in the duty ratio of pwm signal Vpwm, can find out from analog waveform that current drawn I1～I6 value all equates or in certain error range (promptly reaching current balance type), the brightness that lamp string 11～16 is provided equates or in certain error range.Please,, supply voltage VCC, can find out from analog waveform that current drawn I1～I6 value all less than changing, proves that the LED current balance circuit that the embodiment of the invention provides has strong anti-electric source disturbance characteristic between 4V～15V if existing disturbance again referring to Fig. 6 B.
Fig. 7 is the actual signal survey map of LED current balance circuit shown in Figure 4, and wherein, the LED current balance circuit drives 6 lamp strings 11～16 and the electric current I 1～I6 that flows through lamp string 11～16 is set is 20mA.See also Fig. 7, it is the current waveform that a certain lamp string is flow through in actual measurement under 1%, 25% and 50% condition for the duty ratio at pwm signal Vpwm, and wherein the every lattice unit of abscissa is 20 μ s, and the every lattice unit of ordinate is 20mA.As seen when the pulsewidth of pwm signal Vpwm changes, the electric current that flows through the lamp string can change according to pulsewidth, and current value all can maintain under the 20mA condition in the change process at every turn, and therefore (when being equivalent to the duty ratio change) still has goodish linear effective current adjustment when pulsewidth changes.In addition, electric current I 1～I6 that lamp string 11～16 is flow through in actual measurement is respectively 19.8mA, 19.8mA, 19.9mA, 19.9mA, 20.1 and 20.0mA, so the LED current balance circuit that provides of the embodiment of the invention can provide the current error regulation near 1.5%.
For the dimming mode that the embodiment of the invention provides, above-mentioned for adopting digital dimming (or being called the PWM light modulation), yet also can adopting, the embodiment of the invention simulates light modulation (or being called the direct current light modulation).Because in supply voltage VCC value during less than the constant current threshold value, the first bipolar transistor Q1 ends, the reference current Iref value of reference current generator 32 outputs is determined by supply voltage VCC value, therefore can realize simulating light modulation by variable supply voltage VCC as dim signal.When adopting the simulation light modulation, the circuit that is used for digital dimming in the light adjusting circuit 36 must make it lose efficacy, and for example the pwm signal Vpwm that light modulation end DIM is received is provided with the permanent high level that is.
In addition, the embodiment of the invention also can adopt numeral and simulation mixing light modulation to reach higher brightness contrast, and instead be coupled to light modulation end DIM with supply voltage VCC this moment, and receive pwm signal Vpwm by light modulation end DIM.In the duty ratio (as 50%) of pwm signal Vpwm during greater than duty cycle threshold (as 20%), pwm signal Vpwm level during the high level activation is a constant voltage and greater than the constant current threshold value, is equivalent to only adopt digital dimming this moment.In the duty ratio (as 10%) of pwm signal Vpwm during less than duty cycle threshold (as 20%), pwm signal Vpwm level during the high level activation is variable and less than the constant current threshold value, and along with pwm signal Vpwm duty ratio is low more, level can be low more during the high level activation, and finer and smoother brightness contrast is arranged when being equivalent in further employing simulation light modulation under the situation that adopts digital dimming so that in low-light level.
In sum, the LED current balance circuit that the embodiment of the invention provides provides the reference current with strong anti-supply voltage disturbance characteristic to produce current drawn to each lamp string for current mirror because of the reference current generator that adopts, and the framework that current mirror adopts is not influenced by the transistor gain ratio, therefore current mirror can be stablized the electric current that each lamp string is flow through in strangulation, and the adding voltage compensating circuit detects each lamp string end-point voltage, so that the forward conduction voltage drop to each lamp string compensates, different forward each lamp string of conduction voltage drop all can be lighted except guaranteeing to have, also can make the electric current balance more that flows through each lamp string, and because of not adopting special LED controller and cost quite cheap and have more competitiveness.
The above only is preferred embodiment of the present invention, and is in order to restriction the present invention, within the spirit and principles in the present invention not all, any modification of being done, is equal to replacement, improvement etc., all should be included within protection scope of the present invention.
Claims (10)
1. led current balancing circuitry, be used to drive a plurality of lamp strings, each lamp string includes the light-emitting diode of a plurality of coupled in series, and first end of each lamp string all is coupled to a lamp string and presses, it is characterized in that this led current balancing circuitry comprises:
One current mirror is used for producing a plurality of current drawn according to a reference current when opening, and each current drawn provides to second end of a corresponding lamp string, makes to flow through each lamp string stream and reach balance, and makes when closing that to flow through each lamp string flow valuve be zero;
One reference current generator, comprise one first bipolar transistor, one adjustable shunt regulator, one first resistance and one second resistance, this adjustable shunt regulator has cathode terminal, anode tap and reference edge, the collector terminal of this first bipolar transistor is coupled to first end of a supply voltage and this first resistance, the base terminal of this first bipolar transistor is coupled to second end of this first resistance and the cathode terminal of this adjustable shunt regulator, the emitter terminal of this first bipolar transistor is coupled to the reference edge of this adjustable shunt regulator and first end of this second resistance, the anode tap of this adjustable shunt regulator is coupled to a ground connection, and second end of this second resistance is exported this reference current; And
One voltage compensating circuit, comprise a plurality of first diodes, one second bipolar transistor, one the 3rd resistance to one the 8th resistance and one first electric capacity, the cathode terminal of each first diode is coupled to second end of a corresponding lamp string, the anode tap of each first diode all is coupled to first end of the 3rd resistance and first end of the 4th resistance, second end of the 3rd resistance is coupled to the reference edge of this adjustable shunt regulator and first end of the 5th resistance, second end of the 4th resistance and second end of the 5th resistance are coupled to the base terminal and the collector terminal of this second bipolar transistor respectively, first end of the 6th resistance and second end are coupled to emitter terminal and this ground connection of this second bipolar transistor respectively, first end of the 7th resistance is coupled to the collector terminal of this second bipolar transistor and first end of this first electric capacity, second end of the 7th resistance is coupled to first end of the 8th resistance, second end of the 8th resistance is coupled to second end and this ground connection of this first electric capacity, first end of the 8th resistance is exported a compensating signal, and this compensating signal is used to adjust this lamp string pressure value.
2. a kind of led current balancing circuitry as claimed in claim 1, it is characterized in that, this current mirror comprises the first transistor and a transistor seconds of a plurality of couplings, each the first transistor and this transistor seconds all have first end, second end and control end, first end of each the first transistor is coupled to second end of a corresponding lamp string so that a corresponding current drawn to be provided, second end that first end of this transistor seconds is coupled to control end and is coupled to this second resistance is to receive this reference current, second end of each the first transistor and this transistor seconds all is coupled to this ground connection, and the control end of each the first transistor and this transistor seconds is coupled to each other.
3. a kind of led current balancing circuitry as claimed in claim 2 is characterized in that, each the first transistor and this transistor seconds are bipolar transistor or are field-effect transistor.
4. a kind of led current balancing circuitry as claimed in claim 2 is characterized in that, second end of each the first transistor and this transistor seconds all is coupled to this ground connection by a corresponding resistance.
5. a kind of led current balancing circuitry as claimed in claim 2 is characterized in that this current mirror is not opened when the control end of this transistor seconds is coupled to this ground connection, and closes when the control end of this transistor seconds is coupled to this ground connection.
6. a kind of led current balancing circuitry as claimed in claim 1, it is characterized in that, this led current balancing circuitry also comprises an over-voltage detection circuit, this over-voltage detection circuit is coupled to second end of each lamp string, be used for exporting when second terminal voltage that detects arbitrary lamp string surpasses an overvoltage threshold rub-out signal, it is zero that this rub-out signal is used to make this lamp string pressure value.
7. a kind of led current balancing circuitry as claimed in claim 6, it is characterized in that, this over-voltage detection circuit comprises a plurality of second diodes, one Zener diode, one the 9th resistance, 1 the tenth resistance and one second electric capacity, the anode tap of each second diode is coupled to second end of a corresponding lamp string, the cathode terminal of each second diode all is coupled to the cathode terminal of this Zener diode, the anode tap of this Zener diode is coupled to first end of the 9th resistance, second end of the 9th resistance is coupled to first end of the tenth resistance and first end of this second electric capacity, second end of the tenth resistance is coupled to second end and this ground connection of this second electric capacity, and first end of the tenth resistance is exported this rub-out signal.
8. a kind of led current balancing circuitry as claimed in claim 1, it is characterized in that, at this supply voltage value during less than a constant current threshold value, this first bipolar transistor ends, this reference current value of this reference current generator output is determined by this supply voltage value, simulates light modulation as dim signal with realization by this variable supply voltage.
9. a kind of led current balancing circuitry as claimed in claim 1, it is characterized in that, at this supply voltage value during greater than a constant current threshold value, this first bipolar transistor conducting and this adjustable shunt regulator operate as normal, this reference current of this reference current generator output constant current, this led current balancing circuitry also comprises a light adjusting circuit, this light adjusting circuit is coupled to this reference current generator and/or this current mirror, be used for receiving a pulse-width signal and according to this pulse-width signal alternately this reference current generator of opening and closing and/or this current mirror from a light modulation termination, by with this pulse-width signal of pulse width variability as dim signal to realize digital dimming.
10. a kind of led current balancing circuitry as claimed in claim 9, it is characterized in that, this supply voltage is coupled to this light modulation end instead, in the duty ratio of this pulse-width signal during greater than a duty cycle threshold, this pulse-width signal level during the high level activation is a constant voltage and greater than this constant current threshold value, and in the duty ratio of this pulse-width signal during less than this duty cycle threshold, this pulse-width signal level during the high level activation is variable and less than this constant current threshold value.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 200910261687 CN102111932B (en) | 2009-12-24 | 2009-12-24 | Light-emitting diode current balance circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 200910261687 CN102111932B (en) | 2009-12-24 | 2009-12-24 | Light-emitting diode current balance circuit |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN102111932A true CN102111932A (en) | 2011-06-29 |
| CN102111932B CN102111932B (en) | 2013-10-30 |
Family
ID=44175912
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 200910261687 Expired - Fee Related CN102111932B (en) | 2009-12-24 | 2009-12-24 | Light-emitting diode current balance circuit |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN102111932B (en) |
Cited By (17)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102256418A (en) * | 2011-07-15 | 2011-11-23 | 深圳市华星光电技术有限公司 | PWM (pulse width modulation) dimming circuit |
| CN102510630A (en) * | 2011-11-08 | 2012-06-20 | 南京微盟电子有限公司 | Circuit for reducing mismatch of light emitting diode (LED) constant current controllers of channels |
| CN102510621A (en) * | 2011-10-29 | 2012-06-20 | 魏其萃 | Bias voltage establishing device of controller used for light-emitting diode lighting system |
| CN102709872A (en) * | 2012-05-24 | 2012-10-03 | 华为技术有限公司 | Overvoltage protection control device and method |
| CN102843838A (en) * | 2012-08-31 | 2012-12-26 | 上海遍发电子科技有限公司 | Multipath LED (Light Emitting Diode) current-sharing circuit and LED light |
| WO2013013451A1 (en) * | 2011-07-25 | 2013-01-31 | 深圳市华星光电技术有限公司 | Led backlight drive circuit |
| CN102982771A (en) * | 2012-11-28 | 2013-03-20 | 深圳市华星光电技术有限公司 | Backlight driving circuit and liquid crystal display |
| CN103781235A (en) * | 2012-10-25 | 2014-05-07 | 新绿科技股份有限公司 | LED lighting driver |
| CN103813570A (en) * | 2012-11-09 | 2014-05-21 | 刘芬 | LED brightness balancing control circuit and method, and constant-voltage drive LED lighting system and method |
| US8760076B2 (en) | 2011-07-15 | 2014-06-24 | Shenzhen China Star Optoelectronics Technology Co., Ltd. | PWM dimming circuit with multiple outputting paths of current for multiple LED strings |
| CN104332140A (en) * | 2014-10-28 | 2015-02-04 | 深圳创维－Rgb电子有限公司 | Backlight driving system for regional dimming and regional dimming method |
| TWI477192B (en) * | 2012-08-23 | 2015-03-11 | Tpv Display Technology Xiamen | Dc dimming led driving circuit |
| CN106205509A (en) * | 2016-09-22 | 2016-12-07 | 京东方科技集团股份有限公司 | Drive circuit and driving method, backlight, display device and ignition device |
| CN107197569A (en) * | 2017-07-25 | 2017-09-22 | 合肥惠科金扬科技有限公司 | A kind of LED backlight Drive Protecting Circuit and display device |
| WO2018032722A1 (en) * | 2016-08-16 | 2018-02-22 | 深圳市明微电子股份有限公司 | Universal-voltage constant-current linear led drive circuit |
| CN108551702A (en) * | 2017-10-09 | 2018-09-18 | 东莞市翔实信息科技有限公司 | Unmanned electric light driving control system |
| CN109195267A (en) * | 2018-10-22 | 2019-01-11 | 洪学远 | A kind of Novel DC intelligent LED light source and control system |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101510723A (en) * | 2008-02-14 | 2009-08-19 | 台达电子工业股份有限公司 | Multi-set DC laden current balance power supply circuit |
| CN101534594A (en) * | 2008-03-12 | 2009-09-16 | 奇美电子股份有限公司 | Circuit and method for short-circuit protection of light-emitting diode (LED) lightbars |
-
2009
- 2009-12-24 CN CN 200910261687 patent/CN102111932B/en not_active Expired - Fee Related
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101510723A (en) * | 2008-02-14 | 2009-08-19 | 台达电子工业股份有限公司 | Multi-set DC laden current balance power supply circuit |
| CN101534594A (en) * | 2008-03-12 | 2009-09-16 | 奇美电子股份有限公司 | Circuit and method for short-circuit protection of light-emitting diode (LED) lightbars |
Cited By (27)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US8760076B2 (en) | 2011-07-15 | 2014-06-24 | Shenzhen China Star Optoelectronics Technology Co., Ltd. | PWM dimming circuit with multiple outputting paths of current for multiple LED strings |
| CN102256418B (en) * | 2011-07-15 | 2014-02-19 | 深圳市华星光电技术有限公司 | PWM (pulse width modulation) dimming circuit |
| CN102256418A (en) * | 2011-07-15 | 2011-11-23 | 深圳市华星光电技术有限公司 | PWM (pulse width modulation) dimming circuit |
| WO2013013451A1 (en) * | 2011-07-25 | 2013-01-31 | 深圳市华星光电技术有限公司 | Led backlight drive circuit |
| CN102510621B (en) * | 2011-10-29 | 2014-02-19 | 魏其萃 | Bias voltage establishing device of controller used for light-emitting diode lighting system |
| CN102510621A (en) * | 2011-10-29 | 2012-06-20 | 魏其萃 | Bias voltage establishing device of controller used for light-emitting diode lighting system |
| CN102510630B (en) * | 2011-11-08 | 2014-01-29 | 南京微盟电子有限公司 | Circuit for reducing mismatch of light emitting diode (LED) constant current controllers of channels |
| CN102510630A (en) * | 2011-11-08 | 2012-06-20 | 南京微盟电子有限公司 | Circuit for reducing mismatch of light emitting diode (LED) constant current controllers of channels |
| CN102709872A (en) * | 2012-05-24 | 2012-10-03 | 华为技术有限公司 | Overvoltage protection control device and method |
| CN102709872B (en) * | 2012-05-24 | 2014-09-17 | 华为技术有限公司 | Overvoltage protection control device and method |
| TWI477192B (en) * | 2012-08-23 | 2015-03-11 | Tpv Display Technology Xiamen | Dc dimming led driving circuit |
| CN102843838A (en) * | 2012-08-31 | 2012-12-26 | 上海遍发电子科技有限公司 | Multipath LED (Light Emitting Diode) current-sharing circuit and LED light |
| CN102843838B (en) * | 2012-08-31 | 2015-05-06 | 上海遍发电子科技有限公司 | Multipath LED (Light Emitting Diode) current-sharing circuit and LED light |
| US9220140B2 (en) | 2012-10-25 | 2015-12-22 | Greenmark Technology Inc. | LED lighting driver |
| CN103781235A (en) * | 2012-10-25 | 2014-05-07 | 新绿科技股份有限公司 | LED lighting driver |
| CN103781235B (en) * | 2012-10-25 | 2016-02-03 | 新绿科技股份有限公司 | LED lighting driver |
| CN103813570A (en) * | 2012-11-09 | 2014-05-21 | 刘芬 | LED brightness balancing control circuit and method, and constant-voltage drive LED lighting system and method |
| CN102982771A (en) * | 2012-11-28 | 2013-03-20 | 深圳市华星光电技术有限公司 | Backlight driving circuit and liquid crystal display |
| CN102982771B (en) * | 2012-11-28 | 2016-01-13 | 深圳市华星光电技术有限公司 | A kind of backlight drive circuit and liquid crystal display |
| CN104332140A (en) * | 2014-10-28 | 2015-02-04 | 深圳创维－Rgb电子有限公司 | Backlight driving system for regional dimming and regional dimming method |
| WO2018032722A1 (en) * | 2016-08-16 | 2018-02-22 | 深圳市明微电子股份有限公司 | Universal-voltage constant-current linear led drive circuit |
| CN106205509A (en) * | 2016-09-22 | 2016-12-07 | 京东方科技集团股份有限公司 | Drive circuit and driving method, backlight, display device and ignition device |
| CN106205509B (en) * | 2016-09-22 | 2018-11-13 | 京东方科技集团股份有限公司 | Driving circuit and driving method, backlight, display device and ignition device |
| CN107197569A (en) * | 2017-07-25 | 2017-09-22 | 合肥惠科金扬科技有限公司 | A kind of LED backlight Drive Protecting Circuit and display device |
| CN108551702A (en) * | 2017-10-09 | 2018-09-18 | 东莞市翔实信息科技有限公司 | Unmanned electric light driving control system |
| CN109195267A (en) * | 2018-10-22 | 2019-01-11 | 洪学远 | A kind of Novel DC intelligent LED light source and control system |
| CN109195267B (en) * | 2018-10-22 | 2024-05-28 | 洪学远 | Novel direct current intelligent LED light source and control system |
Also Published As
| Publication number | Publication date |
|---|---|
| CN102111932B (en) | 2013-10-30 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN102111932B (en) | Light-emitting diode current balance circuit | |
| TWI423731B (en) | Light-emitting diode (led) current balance circuit | |
| CN103037597B (en) | Multi-channel LED (Light Emitting Diode) constant current control circuit and LED light source control system | |
| CN102123536B (en) | Light-emitting diode driving circuit | |
| US7633463B2 (en) | Method and IC driver for series connected R, G, B LEDs | |
| CN104753349B (en) | Supply unit and the display device including the supply unit | |
| KR100867551B1 (en) | Led array driving apparatus | |
| KR100771780B1 (en) | Led driving apparatus having fuction of over-voltage protection and duty control | |
| CN101106852B (en) | Current constant and light adjusting control circuit for luminescent LED array | |
| CN102098826B (en) | Light emitting diode light source driving circuit | |
| CN1578095B (en) | Load driving device and portable apparatus utilizing such driving device | |
| CN102088808B (en) | Contact current LED driving circuit of snap switch | |
| US20110157246A1 (en) | Backlight unit, method for driving the same, and liquid crystal display device using the same | |
| Chiu et al. | A high accuracy current-balanced control technique for LED backlight | |
| CN109714869B (en) | Linear adjustment and dimming control circuit for LED illumination driving current | |
| CN107770906A (en) | Mixing for lighting circuit dims | |
| CN103379687A (en) | Semiconductor circuit and semiconductor apparatus | |
| CN101527988B (en) | Light source driver module and circuit | |
| CN109360526A (en) | A kind of LED high-efficiency constant-current control device | |
| CN105657891A (en) | LED drive power supply circuit | |
| WO2018198594A1 (en) | Led driver, and led drive circuit device and electronic equipment that use said led driver | |
| CN202838918U (en) | Multichannel drive equalizer circuit and display panel with circuit | |
| CN205389279U (en) | Light emitting diode (LED) driving power circuit | |
| CN102958240A (en) | light source device and dimming control circuit thereof | |
| CN201044524Y (en) | Constant-current and light-modulation control circuit of light emitting diode array for illumination |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20131030 Termination date: 20141224 |
|
| EXPY | Termination of patent right or utility model |