CN101997412A - Control method - Google Patents
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- CN101997412A CN101997412A CN2009101634431A CN200910163443A CN101997412A CN 101997412 A CN101997412 A CN 101997412A CN 2009101634431 A CN2009101634431 A CN 2009101634431A CN 200910163443 A CN200910163443 A CN 200910163443A CN 101997412 A CN101997412 A CN 101997412A
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Abstract
The invention provides a control method, wherein the control method is applied to an output power supply which is used for controlling a switch type power supply to provide constant current. The switch type power supply comprises a winding which is coupled to an input power supply. The winding is controlled by a switch so as to store energy or release energy. The control method comprises setting the maximum peak value of the current which is flown through the winding as a predetermined value, detecting a discharging time of the winding in a switching period and controlling the switching period of the switch to control the ratio of the charging time to the switching period of the switch at the degree which is approximately equal to a constant value.
Description
Technical field
The present invention relates to the switch type power supplying device (switching-mode power supply, SMPS) and relevant method of operation.
Background technology
SMPS has been the power supply unit that most of consumer electronic device adopted, and it is controlled the energy storage in the winding and release energy by the switching of a power switch, and the out-put supply of requirement up to specification is provided.For example, when underloading (light load) or no-load (no load), SMPS may need to operate in constant-voltage mode (constant voltage mode), provides roughly with the irrelevant constant voltage source of output current size; And when heavy duty (heavy load), then operate in constant-current mode, provide roughly with the just irrelevant constant current source of output voltage.
Fig. 1 is a known SMPS 10, can control the mode of (primary side control) with primary side, and constant-voltage mode and constant-current mode are provided.SMPS 10 is a flyback (flyback) framework.Bridge rectifier (bridge rectifier) 12 is approximately with AC power V
ACRectification is an input power supply V
IN, the primary side winding of transformer 20 (primary winding) 24, power switch 15 and current sense resistor 36 are series at input power supply V
INAnd between the earth connection.When on-off controller 18 made power switch 15 open (ON), primary side winding 24 began to increase energy storage wherein; When on-off controller 18 made power switch 15 cut out (OFF), transformer 20 was released energy by its primary side winding (secondarywinding) 22 and auxiliary winding (auxiliary winding) 25.After the electric energy rectification that rectifier 16 and electric capacity 13 are generally discharged, provide an out-put supply V primary side winding 22
OUTTo output loading 38.Rectifier 28 and electric capacity 34 generally after the electric energy rectification of assisting winding 25 to be discharged, provide an operating power V
CCTo on-off controller 18.Needed electric current when starting resistance (startup resistor) 26 provides on-off controller 18 just to begin; Divider resistance 30 and 32 will assist reflected voltage (reflective voltage) on the winding 25 through after the dividing potential drop, offer on-off controller 18.The cross-pressure of the about corresponding primary side winding 22 of reflected voltage on the auxiliary winding 25, so by divider resistance 30 and 32, on-off controller 18 can be learnt the cross-pressure of primary side winding 22, and power controlling switch 15 according to this.
Fig. 2 shows among a kind of known on-off controller 18a the partial circuit about constant-voltage mode.The voltage that sample circuit (sample/hold circuit) 42 taken a sample when power switch 15 is closed and come from the FB pin has produced feedback voltage V
FBError amplifier (error amplifier) 44 is feedback voltage V relatively
FBWith reference voltage V
REF1After, produce bucking voltage V
COMComparator 50 is bucking voltage V relatively
COMAnd detection voltage V
CS, comparator 52 is electric current deboost V relatively
CS-LIMITAnd detection voltage V
CSThe clock output of comparator 50 and 52 result output and oscillator 46 then all is couple to gate logic control circuit (gate logic controller) 48, uses the pin by GATE, power controlling switch 15.By negative feedback loop, the feedback voltage V of Fig. 2
FBBig appointment is controlled in and equals reference voltage V
REF1
Though do not have to show circuit among Fig. 2 about constant-current mode, in the known technology, the SMPS that many instruction constant-current mode have been arranged with and control method.For example United States Patent (USP) is numbered US 7016204-Close-loop PWM controller for primary-side controlled powerconverters, US7388764-Primary side constant output current controller, US7110270-Method and apparatus for maintaining a constant load current withline voltage in a switch mode power supply, US7505287-On-time control forconstant current mode in a flyback power supply etc.
Summary of the invention
One embodiment of the invention provide a kind of control method, are applicable to control one switch type power supplying device (switching power supply).This switch type power supplying device includes a transformer (transformer), is coupled to an input power supply.This transformer is controlled with energy storage by a switch or is released energy, to produce an out-put supply.This control method includes: an electric capacity is provided; Deposit the difference that an actual quantity of electric charge and is estimated the quantity of electric charge with this electric capacity, wherein, flow through in the switch periods of this actual quantity of electric charge corresponding to this switch total charge dosage of this transformer, this is estimated the quantity of electric charge and estimates for this actual quantity of electric charge total pre-in this switch periods; And, according to the voltage of this electric capacity, change in the follow-up switch periods, this actual quantity of electric charge and this estimate the quantity of electric charge one of them, thereby make in this follow-up switch periods, this actual quantity of electric charge approximates this greatly and estimates the quantity of electric charge.
One embodiment of the invention provide a kind of constant current control method, are applicable to a switch type power supplying device.This switch type power supplying device includes a switch and a winding, is in series and is connected to one to import power supply.This switch type power supplying device provides an out-put supply.This constant current control method includes: one first negative feedback loop is provided, with the detection winding current of this winding of flowing through, and produces one and estimate average current, the flow through average current of this winding of its about correspondence; And, one second negative feedback loop is provided, estimate average current according to this, so that the average output current of this out-put supply is approximately a default average output current value.
One embodiment of the invention provide the method for the average current of a kind of generation one actual current source to represent a winding, are applicable to a switch type power supplying device (switching power supply), and it includes this winding.This method includes: detect the winding current of this winding of flowing through, detect voltage to produce one; Relatively should detect a voltage and an average voltage; When this detects voltage greater than this average voltage, with one first current source to electric capacity charge or discharge; When this detects voltage less than this average voltage, with one second current source to this capacitor discharge or charging; According to the voltage of this electric capacity, change this average voltage; And, according to this average voltage, corresponding this actual current source that produces.
One embodiment of the invention provide a kind of control method, are applicable to that control one switch type power supplying device (switching power supply) provides an out-put supply of constant current.This switch type power supplying device includes a winding and is coupled to an input power supply.This winding is controlled with energy storage by a switch or is released energy.This control method includes: the maximum current peak that makes this winding of flowing through is a preset value; Detect the discharge time of this winding in a switch periods; And, control the switch periods of this switch so that should discharge time and the ratio of the switch periods of this switch approximate a definite value greatly.
One embodiment of the invention provide a kind of constant-current constant-voltage power supply changeover device, include a constant current feedback loop and a constant voltage feedback loop.Wherein this constant current feedback loop and the shared building-out capacitor of this constant voltage feedback loop.
One embodiment of the invention provide a kind of on-off controller, are applicable to a switch type power supplying device (switching power supply).This switch type power supplying device includes a transformer (transformer), is coupled to an input power supply.This transformer is controlled with energy storage by a switch or is released energy, and to produce an out-put supply, this on-off controller includes an electric capacity, a current source and a feedback device are estimated in an actual current source.The actual current that this actual current source correspondence is flowed through this transformer charges to this electric capacity, in a switch periods, produces an actual quantity of electric charge.This estimates current source, and corresponding one estimates electric current, to this capacitor discharge, in this switch periods, produces one and estimates the quantity of electric charge.This feedback device, according to the voltage of this electric capacity, maybe this estimates the quantity of electric charge to change this actual quantity of electric charge, so that after one in the switch periods, this estimates the quantity of electric charge near this actual quantity of electric charge.
One embodiment of the invention provide an on-off controller, are applicable to a switch type power supplying device.This switch type power supplying device includes a switch and a winding, is in series and is connected to one to import power supply.This switch type power supplying device provides an out-put supply.This on-off controller includes one first negative feedback loop and a constant current controller.This first negative feedback loop detects the winding current of this winding of flowing through, and produces one and estimate average current, the flow through average current of this winding of its about correspondence.This constant current controller in order to constitute one second negative feedback loop, is estimated average current according to this, makes the average output current of this out-put supply be approximately a default average output current value.
One embodiment of the invention provide a kind of average voltage detector, are applicable to a switch type power supplying device (switching power supply), and it includes a winding and a current detector.This current detector detects the electric current of this winding of flowing through, and detects voltage to produce corresponding one.This average voltage detector includes an electric capacity, a charging current source, a discharging current source and a updating device.This charging current source is to this electric capacity charging.This discharging current source is to this capacitor discharge.This updating device is adjusted an average voltage with the voltage of this electric capacity.When this detection voltage was higher than this average voltage, this electric capacity was recharged.When this detection voltage was lower than this average voltage, this electric capacity was discharged.
Description of drawings
Fig. 1 is a known switch type power supplying device.
Fig. 2 shows in a kind of known on-off controller the partial circuit about constant-voltage mode.
Fig. 3 is according to an on-off controller of the invention process.
Fig. 4 shows a kind of discharge time of detector.
Fig. 5 shows a kind of constant current controller.
Fig. 6 shows the sequential chart according to the embodiment of Fig. 1 and Fig. 3.
Fig. 7 and Fig. 8 show two kinds of constant current controllers in addition.
Fig. 9 is according to an on-off controller of the invention process.
Figure 10 is according to voltage peak detector of the invention process.
Figure 11 is according to constant current controller of the invention process.
Figure 12 is a voltage current adapter.
Figure 13 and Figure 14 are according to two on-off controllers of the invention process.
Figure 15 is according to an on-off controller of the invention process.
Figure 16 is according to constant current controller of the invention process.
Figure 17 and Figure 18 have shown two average voltage detectors.
Figure 19 is according to another peak value controller of the invention process.
Figure 20 is according to another on-off controller of the invention process.
[main element symbol description]
10 switch type power supplying devices
12 bridge rectifiers
13,34 electric capacity
15 power switchs
16,28 rectifiers
18,18a, 18b, 18c, 18d, 18e, on-off controller
18f
20 transformers
22 primary side windings
24 primary side windings
25 auxiliary windings
26 starting resistances
30,32 divider resistances
36 current sense resistors
38 output loadings
42 sample circuits
44 error amplifiers
46 oscillators
48 gate logic control circuits
50,52 comparators
102,102a detector discharge time
104,104a, 104b, 104c, 310,310a constant current controller
106 voltage-controlled oscillators
108 CS peak value controllers
110 comparators
112 reversers
114 with the door
116 pulse generators
118 actual current sources
120 estimate current source
122,124 electric capacity
126 switches
140,142 comparators
144 counters
146 digital analog converters
202,202a constant current controller
204,204a voltage current adapter
206,206a voltage peak detector
302 error amplifiers
306,306a, 306b average voltage detector
364,366 constant current sources
366,368,382,384 electric capacity
386,388 voltage current adapters
I
SECElectric current
I
CONThe predetermined current value
V
ACAC power
V
CS-AVGAverage voltage
V
INThe input power supply
V
OUTOut-put supply
V
CCOperating power
V
FBFeedthrough voltage
V
REF1, V
REF-CCReference voltage
V
COMBucking voltage
V
CSDetect voltage
V
CS-LIMITThe electric current deboost
V
AUXInduced voltage
V
THCritical voltage
V
CC-CAPVoltage
V
GATEGate voltage
S
DISDischarge signal
S
SMPPulse signal
T
DISDischarge time
V
CTLControl voltage
The T switch periods
Embodiment
For above-mentioned and other purposes of the present invention, feature and advantage can be become apparent, cited below particularlyly go out preferred embodiment, and conjunction with figs., be described in detail below.
For the convenience on illustrating, having function that be equal to or similar will be with the components identical symbolic representation.So the element of identical symbol does not represent that two elements is inevitable identical among the different embodiment.Scope of the present invention should decide with the claimed scope of foundation claims.
Fig. 3 is according to an on-off controller 18b of the invention process, can be replaced in the on-off controller 18 among Fig. 1, realizes the control of constant current and constant voltage.Below explain orally is that the on-off controller 18b that supposes Fig. 3 is used among Fig. 1, and the SMPS 10 of Fig. 1 operates in discontinuous conduction mode (dis-continuous conduction mode, DCM), just in each switch periods, the electric energy of transformer 20 is discharge off fully all.
Constant voltage control operation among the on-off controller 18b, similar with the on-off controller 18a among Fig. 2, can analogize by Fig. 2 by those skilled in the art and learn, no longer repeat at this.
Fig. 3 with Fig. 2 different places have, Fig. 3 has CS peak value controller 108, discharge time detector 102, constant current controller 104 and voltage-controlled oscillator (voltage-controlledoscillator, VCO) 106, and these devices go for the constant current control operation, and the electric current that output loading 38 is obtained is approximately predetermined constant current I
OUT-SET
It is a preset value I that CS peak value controller 108 makes the peak-peak electric current of the primary side winding 22 of flowing through effectively
SEC-SETThe induced voltage V of detector 102 discharge time by FB pin and auxiliary winding 25
AUX, to produce discharge signal S
DIS, as T discharge time that detects primary side winding 22
DISThe result.Constant current controller 104 is according to discharge signal S
DIST discharge time that is provided
DIS, and the switch periods T that provided of Gate pin just can learn among this switch periods T instantly whether to equal the constant current I that is scheduled among this switch periods T by the primary side quantity of electric charge of primary side winding 22 outputs
OUT-SETWhat produced always estimates the quantity of electric charge.If variant, control voltage V
CTLWill be changed, and then change the clock frequency that voltage-controlled oscillator 106 is exported.Reformed clock frequency has influenced next switch periods T, and then has influenced and always estimate the quantity of electric charge in next switch periods, forms a negative feedback loop, and purpose is that the quantity of electric charge of always estimating after making it converges to and equals the primary side quantity of electric charge.Such negative feedback loop can make the average output current of primary side winding 22 converge to and approximate the constant current I that is scheduled to greatly
OUT-SET, reach the purpose that constant current is controlled.
It is preset value I that CS peak value controller 108 can make the peak-peak electric current of the current sense resistor 36 among the Fig. 1 that flows through
PRI-SET, make the peak-peak electric current of the primary side winding 24 of flowing through is preset value I with also being equal to
PRI-SETBecause the peak-peak electric current of primary side winding 24 is to the ratio of the peak-peak electric current of primary side winding 22, can equal the number of turns ratio of 22 pairs of primary side windings 24 of primary side winding, be preset value I so CS peak value controller 108 makes the peak-peak electric current of the primary side winding 22 of flowing through with being equal to
SEC-SETFor instance, CS peak value controller 108 can make and detect voltage V
CSPeak value be not more than electric current deboost V
CS-LIMIT, for example 0.85 volt.A kind of execution mode of CS peak value controller 108 has been disclosed in identical inventor's patent application number 12/275,201, Taiwan patent application case numbering 097129355 and Chinese patent application numbering 200810131240.In above application case, CS peak value controller 108 detects voltage V instantly with one
CSCrest voltage and electric current deboost V
CS-LIMITDifference, then this difference is used for adjusting with detecting voltage V
CSComparative voltage V relatively
CS-USE, the detection voltage V after allowing in the switch periods
CSPeak value is more and more near electric current deboost V
CS-LIMITWhen heavy duty,, detect voltage V through after several switch periods
CSPeak value can converge to and approximate electric current deboost V greatly
CS-LIMITAlso therefore, the peak-peak electric current of primary side winding 22 also can approximate preset value I greatly accordingly
SEC-SET
Figure 19 is another CS peak value controller 500, can make to detect voltage V
CSPeak value approximate peak value stop voltage V greatly
REF-LIMITWhen the CS peak value controller 500 of utilization Figure 19 during in the CS of Fig. 3 peak value controller 108, peak value stop voltage V
REF-LIMITBe exactly electric current deboost V
CS-LIMITIn a switch periods, if detect voltage V among Figure 19
CSPeak value greater than peak value stop voltage V
REF-LIMIT, electric capacity 508 can be charged by current source 510 and draw high voltage V
BIAS, higher V
BIASHave higher electric current I
BIASThe resistance R of flowing through
BIASTherefore, in the next switch periods, detect voltage V
CSPeak value will be lower.If in a switch periods, detect voltage V among Figure 19
CSAlways less than peak value stop voltage V
REF-LIMIT, electric capacity 508 can be by BJT and resistance R
LEAKAGE,, and reduce voltage V slightly with very little current discharge
BIASSo, draw high the detection voltage V of next switch periods slightly
CSPeak value.In the design, the electric current I of current source 510
RThe leakage current that will be caused electric capacity 508 much larger than BJT.After several switch periods, detect voltage V
CSPeak value will approximate peak value stop voltage V greatly
REF-LIMIT.
Fig. 4 shows a kind of discharge time of detector 102a.Discharge signal S
DISDuring in logic high level, the transformer 20 in the presentation graphs 1 is also by rectifier 16, to output loading 38 discharges.When transformer 20 discharges finish, the decline that the induced voltage on the FB pin can be unexpected, so, can detect discharge with this unexpected decline and finish, with decision T discharge time
DISTherefore, among Fig. 4, a voltage and a critical voltage V that comparator 110 compares on the FB pin
THAnd discharge time T
DISIn the time of also only can coming across power switch 15 and close, so among Fig. 4, be connected respectively to the output of comparator 110 and the output of reverser 112 with two inputs of door 114.The input of reverser 112 is connected to the GATE pin.
Fig. 5 shows a kind of constant current controller 104a.Actual current source 118 and the current value ratio (I that estimates current source 120
REAL/ I
EXP) be a preset ratio value N
RATIOActual current source 118 is at discharge signal S
DISDuring for high level in logic, just discharge time T
DISIn, to electric capacity 122 chargings.At T discharge time
DISIn, the charging charge of the 118 pairs of electric capacity 122 in actual current source is called actual quantity of electric charge Q
RFALIn switch periods T, to estimate current source 120 and continue electric capacity 122 discharges, its discharge charge is called and estimates quantity of electric charge Q
ESTPulse generator 116 triggers and sends a pulse signal S when the voltage rising edge of GATE pin
SMP, make electric capacity 124 by switch 126, come the voltage V of sampling capacitor 122
CC-CAP, to produce control voltage V
CTL
Voltage-controlled oscillator among Fig. 3 (voltage-controlled oscillator, VCO) 106, for example, can design along with control voltage V
CTLRaise and reduce its frequency of oscillation, also increased switch periods T simultaneously.
Because it is preset value I that the CS peak value controller 108 among Fig. 3 has made the peak-peak electric current of the primary side winding 22 of flowing through
SEC-SETSo,, can suppose when constant current control and need do the time spent that the top current value of primary side winding 22 is exactly preset value I
SEC-SETIn switch periods T, the primary side quantity of electric charge Q that primary side winding 22 is exported
SEC, can calculate with following formula (1)
Q
SEC＝0.5*I
SEC-SET*T
DIS..........(1)
And the desired constant current I that reaches
OUT-SET, in switch periods T, that is exported always estimates quantity of electric charge Q
OUT, can calculate with following formula (2)
Q
OUT＝I
OUT-SET*T..........(2)
And the result of constant current control operation wishes to reach primary side quantity of electric charge Q exactly
SECEqual always to estimate quantity of electric charge Q
OUT, 0.5*I just
SEC-SET* T
DISEqual I
OUT-SET* T.
Among Fig. 5, actual current source 118 and the current value ratio N that estimates current source 120
RATIO(=I
REAL/ I
EXP) be designed to equal (0.5*I
SEC-SET/ I
OUT-SET), that voltage V
CC-CAPVariation behind switch periods T (is defined as Δ V
CC-CAP) can learn by the following derivation of equation:
ΔV
CC-CAP
＝(Q
REAL-Q
EST)/C
CC-CAP
＝(I
REAL*T
DIS-I
EXP*T)*K
1
＝(0.5*I
SEC-SET*T
DIS-I
OUT-SET*T)*K
2------(3)
＝(Q
SEC-Q
OUT)*K
2 ------(4)
Wherein, K
1With K-
2Be two constants (constant), C
CC-CAPCapacitance for electric capacity 122.
Suppose behind switch periods T instantly voltage V
CC-CAPRise, just Δ V
CC-CAPGreater than zero, that according to formula (4) but inference, instantly among this switch periods T, the primary side quantity of electric charge Q that is produced
SECSurpass and always estimate quantity of electric charge Q
OUT, just Shi Ji output current is the constant current I that reaches greater than desired
OUT-SETInstantly behind the switch periods T, voltage V
CC-CAPRising will cause controlling voltage V
CTLRising, and cause the increase of switch periods T next time.So, formed a negative feedback loop.As long as suitably design this negative feedback loop, just can make the result of formula (4) and (5), along with the time goes over, and approach zero.In other words, this negative feedback loop makes T/T by adjusting switch periods T
DISApproximately keep and equal N
RATIO(=I
REAL/ I
EXP), so that Q
SEC-Q
OUT=0, and then reach the purpose that constant current is exported.
Fig. 6 shows the sequential chart according to the embodiment of Fig. 1 and Fig. 3, wherein, from top to bottom, is respectively the gate voltage V on the GATE pin
GATE, the detection voltage V on the CS pin
CS, induced voltage V
AUX, flow through the electric current I of primary side winding 22
SEC, discharge signal S
DIS, pulse signal S
SMP, control voltage V
CTL, and the voltage V of electric capacity 122
CC-CAPAt time t
1The time, gate voltage V
GATERise, opened power switch 15, transformer 20 begins charging, so detect voltage V
CSBegin to rise.Gate voltage V
GATERising edge also triggered pulse signal S
SMPPulse, produce by sampling voltage V
CC-CAPAnd the control voltage V that produces
CTLAt this moment, thus electric capacity 122 by the voltage V that discharges at leisure
CC-CAPDescend gradually.At time t
2The time, gate voltage V
GATEDecline, can make and detect voltage V
CSEqual electric current deboost V
CS-LIMIT, the peak-peak electric current of the corresponding feasible primary side winding 24 of flowing through is preset value I
PRI-SETAt this moment, the peak-peak electric current I of corresponding primary side winding 24
PRI-SET, the electric current I of the primary side of flowing through winding 22
SECBe preset value I
SEC-SETAt time t
2To time t
3Between T discharge time
DIS, so transformer 20 discharges are discharge signal S
DISBe high logic level.At T discharge time
DISIn, because of the charging current of electric capacity 122 greater than discharging current, so voltage V
CC-CAPRise gradually.At time t
3The time, electric current I
SECDischarge off cause induced voltage V
AUXUnexpected decline, so define T discharge time
DIS, and electric capacity 122 stops by current charges.At time t
3Begin to the next time discharge time before, so electric capacity 122 is by the voltage V that discharges at leisure
CC-CAPDescend gradually.At time t
4The time, enter next switch circulation, gate voltage V
GATERise, carry out and time t
1The same action.By Fig. 6 and previous explanation as can be known, control voltage V
CTLRising, can increase switch periods T next time, allow control voltage V after the circulation of next switch
CTLFewer or the minimizing of rising.Such negative feedback loop can make control voltage V at last
CTLRoughly be stable at a stationary value.
Fig. 7 shows another kind of constant current controller 104b, and itself and Fig. 5 are similar, can reach the similar purpose with Fig. 5.Different with Fig. 5, Fig. 7 has comparator 140, and its main purpose is by pulse signal S
SMPIn the defined burst length, compare the voltage V of electric capacity 122
CC-CAPWith reference voltage V
REF-CC, and tool is controlled voltage V to produce charging or discharging current and adjust
CTLFor example, if at pulse signal S
SMPDuring defined burst length, found voltage V
CC-CAPBe higher than reference voltage V
REF-CC, that comparator 140 just charges to electric capacity 124 in the burst length, makes control voltage V
CTLA little rising, and then a little switch periods T that increases next time.
Fig. 8 shows another kind of constant current controller 104c, and itself and Fig. 7 are similar, can reach the similar purpose with Fig. 7.Different with Fig. 7, Fig. 8 has comparator 142, counter 144 and digital analog converter 146.Counter 144 is by gate voltage V
GATERising edge trigger, and according to number in the output of comparator 142 at that time or number down.146 numeral outputs with counter 144 of digital analog converter change into simulation output, as control voltage V
CTLFor example, if at gate voltage V
GATERising edge the time, found voltage V
CC-CAPBe higher than reference voltage V
REF-CC, that counter 144 is just last several 1, and institute is so that control voltage V
CTLA little rising, and then a little switch periods T that increases next time.
Among the embodiment of above Fig. 5, Fig. 7 and Fig. 8, use single electric capacity 122 to write down actual quantity of electric charge Q
REALAnd estimate quantity of electric charge Q
ESTPoor, have a benefit at least: the capacitance variation of electric capacity 122 can't influence control voltage V
CTLRise or downward trend.So, the capacitance variation of the embodiment tolerable electric capacity 122 of Fig. 5, Fig. 7 and Fig. 8.
Fig. 9 is according to an on-off controller 18c of the invention process, can be replaced in the on-off controller 18 among Fig. 1, realizes constant current and constant voltage control operation.Below explaining orally is that the on-off controller 18c of supposition Fig. 9 is used among Fig. 1, and the SMPS 10 of Fig. 1 be operate in discontinuous conduction mode (dis-continuous conduction mode, DCM).
Fig. 9 has following points with the different place of Fig. 3.1) Fig. 9 does not have CS peak value controller 108, but adopts with the same comparator 52 of Fig. 2, comes rough qualification to detect voltage V
CSPeak value.Because signal delay and detection voltage V
CSThe problem of rate of change or the like when comparator 52 effects cause power switch 15 to be closed, can't make and detect voltage V
CSVoltage peak V
CS-PEAKJust equal electric current deboost V
CS-LIMIT2) voltage peak detector 206 that Fig. 9 is many was used for detecting when 15 pent moments of power switch, detected voltage V
CSVoltage peak V
CS-PEAKAnd 3) the constant current controller 202 of Fig. 9 is according to discharge signal S
DISAnd voltage peak V
CS-PEAK, adjust control signal V
CTL
Figure 10 is according to voltage peak detector 206a of the invention process, applicable to the embodiment of Fig. 9.Among Figure 10, pulse generator and switch make electric capacity at gate voltage V
GATERising edge the time make zero.When detecting voltage V
CSWhen increasing along with the opening time increase of power switch 15, the voltage of electric capacity can followed detection voltage V
CSThe voltage peak detector 206a of Figure 10 technical field for this reason has the general knowledge person can understand, and is not going to repeat.
Figure 11 is according to constant current controller 202a of the invention process, applicable to the embodiment among Fig. 9.The constant current controller 202a of Figure 11, with voltage current adapter 204, the actual current source 118 among the constant current controller 104a of replacement Fig. 5.Voltage current adapter 204 is with voltage peak V
CS-PEAKConvert to and correspondingly have value for I
CSS-PEAKElectric current.I
CSS-PEAKCorresponding voltage peak value V
CS-PEAK, its correspondence is the current peak I of switch periods by primary side winding 22 instantly
SEC-PEAKIn other words, I
CSS-PEAKMeeting and current peak I
SEC-PEAKProportion relation.The sequential operation of Figure 11 can allow those skilled in the art understand according to the explanation of Fig. 5, is not going to repeat.
In the design of Figure 11, can make I
CSS-PEAK/ I
SEC-PEAK=I
EXP/ I
OUT-SETSo, Δ V
CC-CAP(be voltage V
CC-CAPVariation behind switch periods T) can learn by the following derivation of equation:
ΔV
CC-CAP
＝(Q
REAL-Q
EST)/C
CC-CAP
＝(0.5*I
CSS-PEAK*T
DIS-I
EXP*T)*K
3
＝(0.5*I
SEC-PEAK*T
DIS-I
OUT-SET*T)*K
4------(5)
＝(Q
SEC-Q
OUT)*K
4 ------(6)
Wherein, K
3With K
4Be two constants.The result who is similar to formula (3) and (4) by formula (5) and (6) can find, if suitable design one negative feedback loop, in Fig. 9, control voltage V
CTLControl voltage-controlled oscillator 106 can be so that the result of formula (5) and (6) approaches 0 gradually, and reaches the purpose of constant current operation.
Figure 12 is a voltage current adapter 204a, and technical field has the general knowledge person can understand thus, is not going to repeat.
As the constant current controller 104a of Fig. 5 the variation of Fig. 7 and Fig. 8 can be arranged, the constant current controller 202a of Figure 11 also can have similar variation.For example, a kind of embodiment of the constant current controller 202 that is applicable to Fig. 9 can be the same with Fig. 7 or Fig. 8, and just the actual current source 118 among Fig. 7 or Fig. 8 replaces with the voltage current adapter 204 of Figure 11.
In Fig. 9, constant current controller 202 is by adjusting the frequency of oscillation of voltage-controlled oscillator 106, just change the switch periods T in the formula (5), wishes to make that the result of formula (5) approaches 0 after the next switch periods.
Except changing this method of frequency of oscillation, also built-in oscillation frequency approximately by changing the current peak of the primary side winding 24 of flowing through in next switch periods, just changes voltage peak V then
CS-PEAKMethod, reach constant current operation.And change voltage peak V
CS-PEAKThe constant current control method, be schematically illustrated in on-off controller 18d, 18e and 18g among Figure 13, Figure 14 and Figure 20.
Figure 13 and Fig. 9 are similar.Different with Fig. 9, the control voltage V of the constant current controller 202 of Figure 13
CTLIt is an input delivering to error amplifier 302.Control voltage V
CTLWith feedback voltage V
FBIn than higher one, can follow reference voltage V-
REF1Relatively.When constant current controller 202 is judged the average output current of primary side winding 22 instantly when too high, control voltage V
CTLRise, and then reduce the bucking voltage V that error amplifier 302 is exported
COMLower bucking voltage V
COM, can limit or reduce the voltage peak V of next switch periods
CS-PEAKThe constant current controller 202 of Figure 13 provides a negative feedback loop, can reach the constant current control operation.The negative feedback loop of constant current control operation, the sequencing of basis signal includes constant current controller 202, error amplifier 302, comparator 50, gate logic control circuit 48, power switch 15 and voltage peak detector 206.And the negative feedback loop of the constant voltage control operation that is provided among Figure 13, the sequencing of basis signal includes sample circuit 42, error amplifier 302, comparator 50, gate logic control circuit 48, power switch 15 and auxiliary winding 25.Generally speaking, the output of the error amplifier among Figure 13 302 has the building-out capacitor (compensationcapacitor) (as shown in the figure) of connection.In the embodiment of Figure 13, the negative feedback loop of constant current control operation is with shared this building-out capacitor of the negative feedback loop of constant voltage control operation.This building-out capacitor is built among the integrated circuit of realizing on-off controller 18d in can being, or is external in outside the integrated circuit.During the constant current operation, feedback voltage V
FBBe lower than control voltage V
CTLSo, control voltage V
CTLControlled building-out capacitor.In other words, during the constant current operation, the negative feedback loop of constant current control operation has been controlled building-out capacitor, and the negative feedback loop of constant voltage control operation does not then have.When constant voltage is operated, control voltage V
CTLBe lower than feedback voltage V
FBSo, feedback voltage V
FBControlled building-out capacitor.
Figure 14 and Fig. 9 are similar.Different with Fig. 9, the control voltage V of the constant current controller 202 of Figure 14
CTLDeliver to an adder.Control voltage V
CTLWith detecting voltage V
CSThe result of addition, one of device 52 input as a comparison is with electric current deboost V
CS-LIMITCompare.When constant current controller 202 is judged the average output current of primary side winding 22 instantly when too high, control voltage V
CTLRise, and then drawn high the starting voltage value of an input of comparator 52, also reduced the voltage peak V of next switch periods
CS-PEAKSo the average output current of the primary side winding 22 of following one-period will be lowered.
Figure 20 and Figure 13 are similar.The constant current controller 203 of Figure 20 can have the same internal circuit with the constant current controller 202 of Figure 13, and just an input of constant current controller 203 receives bucking voltage V
COM, and the corresponding input of constant current controller 202 receives voltage peak V
CS-PEAKCS peak value controller 51 among Figure 20 makes and detects voltage V
CSPeak value along with the increase of switch periods, and approximate bucking voltage V greatly
COMCS peak value controller 51 can adopt the CS peak value controller 500 of Figure 19 or the CS peak value controller of Fig. 3 108 to implement.Constant current controller 203 among Figure 20 is with instantly bucking voltage V
COMAnd discharge signal S
DISJudge that output current actual in the switch periods instantly is with the desired constant current I that reaches
OUT-SETComparative result, adjust the bucking voltage V of next switch periods according to this
COMAnd bucking voltage V
COMCan influence voltage peak V
CS-PEAKSo, influenced actual output current.The negative feedback loop of the constant current control operation among Figure 20, the sequencing of basis signal includes constant current controller 203, error amplifier 302 and CS peak value controller 51.
Above embodiment be the SMPS 10 of Fig. 1 operate in discontinuous conduction mode (dis-continuousconduction mode, DCM) under, reach the operation of constant current control.Following embodiment will introduce the SMPS 10 that how to make Fig. 1 operate in continuous conduction mode (continuous conduction mode, CCM) under, also can reach the operation that constant current is controlled.
Figure 15 is according to an on-off controller 18f of the invention process, can be replaced in the on-off controller 18 among Fig. 1, realizes under the CCM constant current and constant voltage control operation.
Figure 15 and Figure 13 are similar.Different with Figure 13, Figure 15 does not have the detector 102 discharge time among Figure 13; Constant current controller 310 among Figure 15 has a littlely and changes; And, the voltage peak detector 206 that Figure 15 replaces among Figure 13 with average voltage detector 306.
Figure 15 do not need one discharge time detector decide T discharge time
DIS, because under CCM, the shut-in time T of power switch 15
OFFBe exactly T discharge time
DIS
Under CCM, by the primary side quantity of electric charge Q of primary side winding 22 outputs
SECShould be 0.5 (I
SEC-PEAK+ I
SEC-VALLEY) * T
DIS=I
SEC-AVG* T
OFF, I wherein
SEC-PEAK, I
SEC-VALLEYWith I
SEC-AVGBe respectively current peak, electric current valley and the current average of primary side winding 22 in the switch periods instantly.From the derivation of formula (5) and (6), can find current peak I
SEC-PEAKCorrespond to voltage peak V
CS-PEAKSo, current average I
SEC-AVGWill correspond to average voltage V
CS-AVGTherefore, the average voltage detector 306 among Figure 15 is found out average voltage V
CS-AVG, give constant current controller 310 and reach the constant current control operation.
Figure 16 is according to constant current controller 310a of the invention process, applicable to the embodiment of Figure 15.In Figure 16, average voltage V
CS-AVGConvert to by voltage current adapter 360 and to have value for I
CSS-AVGElectric current.Voltage current adapter 360 can be implemented with the voltage current adapter 204a of similar Figure 12.In the design of Figure 16, should make I
CSS-AVG/ I
SEC-AVG=I
EXP/ I
OUT-SETThe constant current control operation of similar Figure 13 is as long as can find average voltage V
CS-AVG, Figure 15 provides a negative feedback loop, reaches the constant current control operation.
As the constant current controller 104a among Fig. 5 the variation of Fig. 7 and Fig. 8 is arranged, the constant current controller 310a among Figure 16 can similarly change.Though do not show with diagram, this variation can be analogized and learnt by previous explanation, no longer repeats.
Figure 17 has shown an average voltage detector 306a, in the on-off controller 18f among Figure 15.The average voltage detector 306a oneself provide a negative feedback loop, makes average voltage V
CS-AVGApproximate the average voltage of primary side winding 24 when power switch 15 is opened greatly.Electric capacity 368 has been remembered average voltage V
CS-AVG, also be the voltage initial value of electric capacity 366 when power switch 15 is opened.As power switch 15 unlatching, just gate voltage V
GATEDuring in logic high level, if detect voltage V
CSBe lower than average voltage V
CS-AVG, then constant current source 364 is with predetermined current value I
CONTo electric capacity 366 discharges; If detect voltage V
CSBe higher than average voltage V
CS-AVG, then constant current source 362 is with predetermined current value I
CONTo electric capacity 366 chargings.In other words, at power switch in 15 opening times, if detect voltage V
CSThe electric current of primary side winding 24 (correspondence flow through) is higher than average voltage V
CS-AVGThe time of (corresponding primary side winding 24 average currents of conjecture at present) is greater than being lower than average voltage V
CS-AVGTime, the voltage of that electric capacity 366 will raise.So, when power switch 15 1 is closed, since the effect that electric charge is shared, the average voltage V of electric capacity 368
CS-AVGCan be by a little drawing high.Average voltage V
CS-AVGVariation can make in following one-period, detect voltage V
CSBe higher than average voltage V
CS-AVGBe lower than average voltage V around
CS-AVGTime.The average voltage V that electric capacity 368 is remembered
CS-AVGIf no longer change, just mean detection voltage V
CSBe higher than average voltage V
CS-AVGTime with being lower than average voltage V
CS-AVGTime the same.At this moment, average voltage V
CS-AVGJust really represented detection voltage V
CSMean value.
Figure 18 has shown another average voltage detector 306b, in the on-off controller 18f among Figure 15.The average voltage detector 306b also provide a negative feedback loop, makes average voltage V
CS-AVGApproximate the average voltage of primary side winding 24 when power switch 15 is opened greatly.Similarly, electric capacity 382 has been remembered average voltage V
CS-AVGThe effect of voltage current adapter 386 and electric capacity 384 is to calculate to detect voltage V
CSIntegrated value S when power switch 15 is opened
VCSThis integrated value S
VCSCan correspond in a switch periods the actual quantity of electric charge of the primary side of flowing through winding 24.The effect of voltage current adapter 388 and electric capacity 384 is to calculate average voltage V
CS-AVGIntegrated value S when power switch 15 is opened
VCSAVGThis integrated value S
VCSAVGCan be considered as the quantity of electric charge of estimating of the actual quantity of electric charge.If integrated value S
VCSGreater than integrated value S
VCSAVG, the voltage of electric capacity 384 will be raised, and also represents average voltage V simultaneously
CS-AVGOn the low side.So, when power switch 15 is closed, because electric charge is shared the principle of (charge sharing), average voltage V
CS-AVGBy a little increase.So, make in following one-period integrated value S
VCSAVGTo integrated value S
VCSApproaching.Average voltage V
CS-AVGGenerally, make integrated value S by certain value of lock
VCSApproximate integrated value S greatly
VCSAVG, also mean average voltage V
CS-AVGApproximate greatly and detect voltage V
CSMean value.
Adjust average voltage V among Figure 17 and Figure 18
CS-AVGMode, adjust control voltage V among similar Fig. 5
CTLMode.Adjust control voltage V in the simulation drawing 7
CTLMode, Figure 17 and Figure 18 also can be with the voltages of electric capacity 366 or 384, with a reference voltage V
REF-AVGRelatively, use its comparative result then, electric capacity 368 or 382 is discharged and recharged trim voltage mean value V with electric current
CS-AVGSuch negative feedback loop also can equally reach and find about average voltage V
CS-AVGEffect.
Simulate and in Fig. 8, adjust control voltage V
CTLMode, Figure 17 and Figure 18 also can be with the voltages of electric capacity 366 or 384, with a reference voltage V
REF-AVGRelatively, use its comparative result then, make number or following number on the counter, finely tune the average voltage V that a digital analog converter is exported
CS-AVGSo, electric capacity 368 or 382 just can omit.Such negative feedback loop also can equally reach and find about average voltage V
CS-AVGEffect.
Though above embodiment implements with the flyback framework, the present invention is defined in to be suitable for the flyback framework, also goes for the power supply changeover device framework of other types such as booster or buck.
Though the present invention with preferred embodiment openly as above; right its is not in order to qualification the present invention, those skilled in the art, without departing from the spirit and scope of the present invention; when can doing a little change and retouching, so protection scope of the present invention is as the criterion when looking the appended claims person of defining.
Claims (10)
1. a control method is applicable to control one switch type power supplying device, and this switch type power supplying device includes a transformer, be coupled to an input power supply, this transformer is controlled with energy storage by a switch or is released energy, and to produce an out-put supply, this control method includes:
One electric capacity is provided;
Deposit the difference that an actual quantity of electric charge and is estimated the quantity of electric charge with this electric capacity, wherein, flow through in the switch periods of this actual quantity of electric charge corresponding to this switch total charge dosage of this transformer, this is estimated the quantity of electric charge and estimates for this actual quantity of electric charge total pre-in this switch periods; And
According to the voltage of this electric capacity, change in the follow-up switch periods, this actual quantity of electric charge and this estimate the quantity of electric charge one of them, thereby make in this follow-up switch periods, this actual quantity of electric charge approximates this greatly and estimates the quantity of electric charge.
2. control method as claimed in claim 1, wherein, this transformer has a primary side winding and a primary side winding, and this actual quantity of electric charge is corresponding to the primary side quantity of electric charge of this primary side winding of flowing through in this switch periods.
3. control method as claimed in claim 2, wherein, this control method also includes:
One preset value is provided;
Make the peak-peak electric current of this primary side winding of flowing through be approximately this preset value;
Provide an actual current source and to estimate current source, wherein this actual current source ratio is in this preset value;
Detect the discharge time of this primary side winding in a switch periods;
Come from first electric charge of in this discharge time this electric capacity charging being accumulated generation with this actual current, as this actual quantity of electric charge; And
Estimate electric current with this and come from second electric charge of in this switch periods this capacitor discharge being accumulated, estimate the quantity of electric charge as this; And
According to the voltage of this electric capacity, change this preset value.
4. control method as claimed in claim 2, wherein, this control method also includes:
The peak-peak electric current that makes this primary side winding of flowing through is a preset value;
Provide an actual current source and to estimate current source, wherein this actual current source and this current value of estimating current source are a preset ratio value;
Detect the discharge time of this primary side winding in a switch periods;
Come from first electric charge of in this discharge time this electric capacity charging being accumulated generation with this actual current, as this actual quantity of electric charge; And
Estimate electric current with this and come from second electric charge of in this switch periods this capacitor discharge being accumulated, estimate the quantity of electric charge as this.
5. control method as claimed in claim 2, wherein, this control method also includes:
Provide an actual current source and to estimate current source, wherein the about correspondence of the current value in this actual current source current peak or the current average of this primary side winding of flowing through;
Accumulate this actual current with this electric capacity and come from first electric charge that is produced in the discharge time, as this actual quantity of electric charge; And
Accumulate this with this electric capacity and estimate electric current and come from second electric charge that is produced in the switch periods, estimate the quantity of electric charge as this.
6. control method as claimed in claim 5, wherein, this conversion step includes;
This voltage according to this electric capacity changes a control signal;
Relatively this control signal and a reference signal are to produce a compensating signal; And
With this compensating signal, limit this primary side current peak of this primary side winding of flowing through.
7. control method as claimed in claim 5 also includes:
This voltage according to this electric capacity changes a control signal; And
According to this control signal, limit this primary side current peak of this primary side winding of flowing through.
8. control method as claimed in claim 5 also includes:
Detect this primary side winding this discharge time in a switch periods.
9. control method as claimed in claim 1, wherein, this actual quantity of electric charge is corresponding to the primary side quantity of electric charge of this primary side winding of flowing through in this switch periods.
10. control method as claimed in claim 9, wherein, this control method also includes:
Provide an actual current source and to estimate current source, wherein the electric current correspondence in this actual current source electric current of this primary side winding of flowing through;
Accumulate this actual current with this electric capacity and come from first electric charge that is produced when this switch opens, as this actual quantity of electric charge; And
Accumulate this with this electric capacity and estimate electric current and come from second electric charge that is produced when this switch opens, estimate the quantity of electric charge as this;
Wherein, this conversion step includes:
This voltage according to this electric capacity changes this and estimates current source, estimates the quantity of electric charge to change in this follow-up switch periods this.
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| US10686373B2 (en) | 2015-05-15 | 2020-06-16 | On-Bright Electronics (Shanghai) Co., Ltd. | Systems and methods for output current regulation in power conversion systems |
| US10270334B2 (en) | 2015-05-15 | 2019-04-23 | On-Bright Electronics (Shanghai) Co., Ltd. | Systems and methods for output current regulation in power conversion systems |
| US10003268B2 (en) | 2015-05-15 | 2018-06-19 | On-Bright Electronics (Shanghai) Co., Ltd. | Systems and methods for output current regulation in power conversion systems |
| US10811965B2 (en) | 2015-05-15 | 2020-10-20 | On-Bright Electronics (Shanghai) Co., Ltd. | Systems and methods for output current regulation in power conversion systems |
| US10432096B2 (en) | 2015-05-15 | 2019-10-01 | On-Bright Electronics (Shanghai) Co., Ltd. | Systems and methods for output current regulation in power conversion systems |
| US9960674B2 (en) | 2015-05-15 | 2018-05-01 | On-Bright Electronics (Shanghai) Co., Ltd. | Systems and methods for output current regulation in power conversion systems |
| US11652410B2 (en) | 2015-05-15 | 2023-05-16 | On-Bright Electronics (Shanghai) Co., Ltd. | Systems and methods for output current regulation in power conversion systems |
| CN107742983A (en) * | 2017-11-29 | 2018-02-27 | 上海南麟电子股份有限公司 | Share constant current constant voltage control module, reduction voltage circuit and the compensation method of compensation |
| CN107742983B (en) * | 2017-11-29 | 2023-05-26 | 上海南麟电子股份有限公司 | Constant-current constant-voltage control module, voltage reducing circuit and compensation method for sharing compensation |
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