CN101888256A - Multi-mode multi-frequency multi-application direct frequency conversion wireless transceiver - Google Patents
Multi-mode multi-frequency multi-application direct frequency conversion wireless transceiver Download PDFInfo
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- CN101888256A CN101888256A CN2010101375694A CN201010137569A CN101888256A CN 101888256 A CN101888256 A CN 101888256A CN 2010101375694 A CN2010101375694 A CN 2010101375694A CN 201010137569 A CN201010137569 A CN 201010137569A CN 101888256 A CN101888256 A CN 101888256A
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Abstract
The invention discloses a multi-mode multi-frequency multi-application direct frequency conversion wireless transceiver framework capable of supporting WLAN802.11a/b/g (wireless local area network), GSM (global system for mobile communication), UHF RFID (radio frequency identification) and TD-SCDMA (time division-synchronous code division multiple address) at the same time. The wireless transceiver comprises a 0.8-2.1 GHz wireless transceiving module, a local multi-mode multi-frequency phase lock loop frequency synthesis module and a 2.4/5 GHz wireless transceiving module. The transceiver supports three communication modes of TD-SCDMA, UHF RFID and GSM by adopting a signal transceiving path of a 0.8-2.1 GHz wideband orthogonal direct frequency conversion structure, integrates the 5 GHz orthogonal direct frequency conversion signal transceiving path of the WLAN 802.11a mode and the 2.4 GHz orthogonal direct frequency conversion signal transceiving path of the WLAN 802.11b/g mode in the base band, and supports the WLAN 802.11a/b/g mode at the same time. The transceiver provides a local frequency source for all communication modes by adopting a single low-phase noise phase lock loop frequency synthesizer and meets the requirement of up/down frequency conversion.
Description
Technical field
It is particularly a kind of to support UHF RFID (radio frequency identification), TD-SCDMA (TD SDMA), GSM (global system for mobile communications), WLAN 802.11a/b/g (WLAN) multimode, multifrequency and many application Direct Conversion structure wireless transceivers simultaneously the present invention relates to a kind of wireless transceiver.
Background technology
Emerged in an endless stream with fast-developing, the new technology and standard of wireless communication technology, user is wished to by the wireless terminal in hand, corresponding network is accessed anywhere or anytime according to the need for oneself, the communication that flexible, convenient, absolute liBerty is linked up is realized, the development trend of future wireless system is the continuous integration between various technologies.
First, Ubiquitous network application promotes short distance wireless technical to be merged with Cellular Networks technological direction.Short-distance wireless communication technology is used for logistics and consumer electronics sector always, mainly realizes charging and monitoring function.In recent years, with the development of the communication technology and integrated circuit technique, the short distance wireless technical such as UHF RFID starts to combine with honeycomb network technology, and has derived a series of new business.It is secondly, mobile that gradually trend is merged in complementary and competition with broadband wireless technology.The continuing to develop of mobile communication, broadband services increase rapidly and Wi-Fi business success, facilitate the birth of the various broadband wireless technologies such as OFDM.On the other hand, OFDM appearance has promoted the progress of 3G Enhanced Technologies again.At present, numerous mobile phones and intelligent terminal manufacture commercial cities start the Devoting Major Efforts To Developing 3G/WiFi bimodulus even mould mobile phones of 2G/3G/Wi-Fi tri-, and these compatible wireless technologys intelligent terminal, and succeeded application in some countries.
Further to realize the complete warm of a variety of wireless technologys under different scenes, it is desirable to have covering WLAN, 2G/3G seamless connections are realized, while completely supporting that super high frequency radio frequency recognizes multimode, multifrequency and many employing wireless transceivers of frequency range.
The content of the invention
The purpose of the present invention is that design one kind can be while support the wireless transceiver of WLAN 802.11a/b/g (WLAN), GSM (global system for mobile telecommunications), UHF RFID (radio frequency identification) and TD-SCDMA (TD SDMA) various modes GSM.
To achieve these goals, the technical scheme is that supporting TD-SCDMA by using 0.8-2.1GHz receiving and transmitting signals path on the basis of conventional single-mode Direct Conversion wireless transceiver as shown in Figure 1, UHFRFID, tri- kinds of transceiver modes of GSM, and the 5GHz receiving and transmitting signals path of WLAN802.11a patterns is integrated with the 2.4GHz receiving and transmitting signals path of WLAN802.11b/g patterns in base band, whole system employs the low noise phase-locked loop frequency integrator that can provide multiband as local oscillator.
The object of the present invention is achieved like this：
A kind of multi-mode multi-frequency multi-application direct frequency conversion wireless transceiver, the wireless transceiver includes 0.8-2.1GHz radio receiving transmitting modules A, the local parts of multimode multi-frequency phase-locked loop frequency integration module B and 2.4/5GHz radio receiving transmitting module C tri-.Wherein 0.8-2.1GHz radio receiving transmitting modules A includes 0.8-2.1GHz frequency range duplexers U1 on the receive path, 0.8-2.1GHz receiving radio frequency front end bandpass filters U2, 0.8-2.1GHz receiving radio frequency front end low-noise amplifiers U3, 0.8-2.1GHz receives Direct-conversion device U4, in-phase channel ABB direct current arrester U5, in-phase channel selection wave filter U6, in-phase channel programmable gain amplifier U7, in-phase channel analog-digital converter U8, orthogonal channel ABB direct current arrester U9, orthogonal channel selection wave filter U10, orthogonal channel programmable gain amplifier U11, orthogonal channel analog-digital converter U12；0.8-2.1GHz radio receiving transmitting modules A is on the transmit path comprising 0.8-2.1GHz transmitting radio-frequency front-end bandpass filter U13,0.8-2.1GHz transmitting RF front-end power amplifier U14,0.8-2.1GHz transmitting Direct conversion devices U15, in-phase channel image-rejection filter U16, in-phase channel variable-gain amplifier U17, in-phase channel digital analog converter U18, orthogonal channel image-rejection filter U19, orthogonal channel variable-gain amplifier U20, orthogonal channel digital analog converter U21；Local multimode multi-frequency phase-locked loop frequency integration module B includes variable connector array U22, the first frequency divider U23, the second frequency divider U24, tri-frequency divider U25, frequency mixer U26, voltage controlled oscillator U27, loop filter U28, Frequency/Phase Discriminator U29, multi-modulus frequency divider U30；2.4/5GHz radio receiving transmitting modules C receives Direct-conversion device U34 on 2.4GHz RX paths comprising 2.4GHz duplexer U31,2.4GHz receiving radio frequency front end bandpass filter U32,2.4GHz receiving radio frequency front end low-noise amplifiers U33,2.4GHz；2.4/5GHz radio receiving transmitting modules C is receiving the shared in-phase channel analog filtering amplifier U35 of base band, in-phase channel analog-digital converter U36, orthogonal channel analog filtering amplifier U37, orthogonal channel analog-digital converter U38；2.4/5GHz radio receiving transmitting modules C receives Direct-conversion device U42 on 5GHz RX paths comprising 5GHz duplexer U39,5GHz receiving radio frequency front end bandpass filter U40,5GHz receiving radio frequency front end low-noise amplifiers U41,5GHz；2.4/5GHz radio receiving transmitting modules C includes 2.4GHz transmitting radio-frequency front-end bandpass filter U43,2.4GHz transmitting RF front-end power amplifier U44,2.4GHz transmitting Direct conversion devices U45 on 2.4GHz transmission paths；2.4/5GHz radio receiving transmitting modules C shares in-phase channel pulse shaping filter U46, in-phase channel digital analog converter U47, orthogonal channel pulse shaping filter U48, orthogonal channel digital analog converter U49 in transmitting baseband；2.4/5GHz radio receiving transmitting modules C includes 5GHz transmitting radio-frequency front-end bandpass filter U50,5GHz transmitting RF front-end power amplifier U51,5GHz transmitting Direct conversion devices U52 on 5GHz transmission paths.
The 0.8-2.1GHz frequency ranges duplexer U1 has a bidirectional end RF1 to be connected with exterior antenna, one output end is connected with 0.8-2.1GHz receiving radio frequency front end bandpass filters U2 input, and an input is connected with the 0.8-2.1GHz output ends for launching radio-frequency front-end bandpass filter U13.
The output end of the 0.8-2.1GHz receiving radio frequency front ends bandpass filter U2 is connected with 0.8-2.1GHz receiving radio frequency front end low-noise amplifiers U3 input.
The difference output end of the 0.8-2.1GHz receiving radio frequency front ends low-noise amplifier U3 is connected with the 0.8-2.1GHz differential input ends for receiving Direct-conversion device U4.
The 0.8-2.1GHz, which receives Direct-conversion device U4, has one to be connected with phase difference output end with in-phase channel ABB direct current arrester U5 differential input end, and an orthogonal differential output end is connected with orthogonal channel ABB direct current arrester U9 differential input end.
The difference output end of the in-phase channel ABB direct current arrester U5 selects wave filter U6 differential input end to be connected with in-phase channel；The difference output end of the in-phase channel selection wave filter U6 is connected with in-phase channel programmable gain amplifier U7 differential input end.
The difference output end of the in-phase channel programmable gain amplifier U7 is connected with in-phase channel analog-digital converter U8 differential input end；The data terminal output end of the in-phase channel analog-digital converter U8 is OUT1.
The difference output end of the orthogonal channel ABB direct current arrester U9 selects wave filter U10 Differential Input to be connected with orthogonal channel.
The difference output end of the orthogonal channel selection wave filter U10 is connected with orthogonal channel programmable gain amplifier U11 differential input end；The difference output end of the orthogonal channel programmable gain amplifier U11 is connected with orthogonal channel analog-digital converter U12 differential input end.
The data terminal output end of the orthogonal channel analog-digital converter U12 is connected for the inputs for launching radio-frequency front-end bandpass filter U13 of 0.8-2.1GHz described in OUT2 with the 0.8-2.1GHz output ends for launching RF front-end power amplifier U14.
The differential input end of the 0.8-2.1GHz transmitting RF front-end power amplifiers U14 is connected with difference output end IT2, IT2B of the 0.8-2.1GHz difference output ends and variable connector array U22 for launching Direct conversion device U15.
The same phase differential input end of the 0.8-2.1GHz transmitting Direct conversion devices U15 is connected with in-phase channel image-rejection filter U16 difference output end, and its orthogonal differential input is connected with orthogonal channel image-rejection filter U19 difference output end.
The differential input end of the in-phase channel image-rejection filter U16 is connected with in-phase channel variable-gain amplifier U17 difference output end.
The differential input end of the in-phase channel variable-gain amplifier U17 is connected with in-phase channel digital analog converter U18 difference output end.
The data input pin of the in-phase channel digital analog converter U18 is IN1.
The differential input end of the orthogonal channel image-rejection filter U19 is connected with orthogonal channel variable-gain amplifier U20 difference output end.
The differential input end of the orthogonal channel variable-gain amplifier U20 is connected with orthogonal channel digital analog converter U21 difference output end.
The data input pin of the orthogonal channel digital analog converter U21 is IN2.
Difference output end IT1, IT1B of the variable connector array U22 is connected with the 0.8-2.1GHz local oscillator differential input ends for receiving Direct-conversion device U4 and 0.8-2.1GHz transmitting Direct conversion device U15.
Difference output end of two differential input ends of the variable connector array respectively with the first frequency divider U23 and the second frequency divider U24 is connected.
The input of the first frequency divider U23 is connected with the second frequency divider U24 positive output end.
The input of the second frequency divider U24 is connected with voltage controlled oscillator U27 output end.
The frequency mixer U26 is using the second frequency divider U24 difference output and voltage controlled oscillator U27 Single-end output as input, and its difference output end is IT4, IT4B, while being connected with tri-frequency divider U25 differential input end.
The difference output end of the tri-frequency divider U25 is IT3, IT3B.
The input of the voltage controlled oscillator U27 is connected with loop filter U28 output end, and output end is connected with a multi-modulus frequency divider U30 input.
The input of the loop filter U28 is connected with Frequency/Phase Discriminator U29 output end.
The input of the Frequency/Phase Discriminator U29 is connected with multi-modulus frequency divider U30 output end.
Two other input of the multi-modulus frequency divider U30 is IN3, IN4, is respectively intended to input increment-summation modulator data and global system for mobile telecommunications GSM transmitting data.
The 2.4GHz duplexers U31 has a bidirectional end RF2 to be connected with exterior antenna, one output end is connected with 2.4GHz receiving radio frequency front end bandpass filters U32 input, and an input is connected with the 2.4GHz output ends for launching radio-frequency front-end bandpass filter U43.
The output end of the 2.4GHz receiving radio frequency front ends bandpass filter U32 is connected with 2.4GHz receiving radio frequency front end low-noise amplifiers U33 input.
The difference output end of the 2.4GHz receiving radio frequency front ends low-noise amplifier U33 is connected with the 2.4GHz differential input ends for receiving Direct-conversion device U34.
The 2.4GHz, which receives Direct-conversion device U34, has one to be connected with phase difference output end with in-phase channel analog filtering amplifier U35 differential input end, and an orthogonal differential output end is connected with orthogonal channel analog filtering amplifier U37 differential input end.
The difference output end of the in-phase channel analog filtering amplifier U35 is connected with in-phase channel analog-digital converter U36 Differential Input.
The data output end of the in-phase channel analog-digital converter U36 is OUT3.
The difference output end of the orthogonal channel analog filtering amplifier U37 is connected with orthogonal channel analog-digital converter U38 Differential Input.
The data output end of the orthogonal channel analog-digital converter U38 is OUT4.
The input of the 2.4GHz transmitting radio-frequency front-end bandpass filters U43 is connected with the 2.4GHz output ends for launching RF front-end power amplifier U44.
The differential input end of the 2.4GHz transmitting RF front-end power amplifiers U44 is connected with the 2.4GHz difference output ends for launching Direct conversion device U45.
The same phase Differential Input of the 2.4GHz transmitting Direct conversion devices U45 is connected with in-phase channel pulse shaping filter U46 difference output end, and orthogonal differential input is connected with orthogonal channel pulse shaping filter U48 difference output end.
The local oscillator differential input end that the 2.4GHz receives Direct-conversion device U34 and 2.4GHz transmitting Direct conversion device U45 is IT3, IT3B.
The differential input end of the in-phase channel pulse shaping filter U46 is connected with in-phase channel digital analog converter U47 difference output end.
The data input pin of the in-phase channel digital analog converter U47 is IN5.
The differential input end of the orthogonal channel pulse shaping filter U48 is connected with orthogonal channel digital analog converter U49 difference output end.
The data input pin of the orthogonal channel digital analog converter U49 is IN6.
The 5GHz duplexers U39 has a bidirectional end RF3 to be connected with exterior antenna, and an output end is connected with 5GHz receiving radio frequency front end bandpass filters U40 input, and an input is connected with the 5GHz output ends for launching radio-frequency front-end bandpass filter U50.
The output end of the 5GHz receiving radio frequency front ends bandpass filter U40 is connected with 5GHz receiving radio frequency front end low-noise amplifiers U41 input.
The difference output end of the 5GHz receiving radio frequency front ends low-noise amplifier U41 is connected with the 5GHz differential input ends for receiving Direct-conversion device U42.
The 5GHz, which receives Direct-conversion device U42, has one to be connected with phase difference output end with in-phase channel analog filtering amplifier U35 differential input end, and an orthogonal differential output end is connected with orthogonal channel analog filtering amplifier U37 differential input end.
The input of the 5GHz transmitting radio-frequency front-end bandpass filters U50 is connected with the 5GHz output ends for launching RF front-end power amplifier U51.
The differential input end of the 5GHz transmitting RF front-end power amplifiers U51 is connected with the 5GHz difference output ends for launching Direct conversion device U52.
The same phase Differential Input of the 5GHz transmitting Direct conversion devices U52 is connected with in-phase channel pulse shaping filter U46 difference output end, and orthogonal differential input is connected with orthogonal channel pulse shaping filter U48 difference output end.
The local oscillator differential input end that the 5GHz receives Direct-conversion device U42 and 5GHz transmitting Direct conversion device U52 is IT4, IT4B.
The present invention realizes that the signal of tri- kinds of communication patterns of TD-SCDMA, UHF RFID, GSM is received using a 0.8-2.1GHz orthogonal Direct-conversion RX path.0.8-2.1GHz wideband low noise amplifier U3 are employed in receiving radio frequency front end, programmable channel selection wave filter U6 and U10, programmable gain amplifier U7 and U11 are employed receiving ABB.The present invention supports that the signal of two kinds of communication patterns of TD-SCDMA, UHF RFID is launched using a 0.8-2.1GHz orthogonal Direct conversion transmission path.0.8-2.1GHz wideband power amplifer U14 are employed in transmitting radio-frequency front-end, image-rejection filter U16 and U19, change programming gain amplifier U17 and U20 are employed in launching simulation base band.For GSM mode, the present invention realizes digital modulation in local multimode multi-frequency phase-locked loop frequency integration module B multi-modulus frequency divider U30 input input signals in the way of directly controlling local oscillation signal.
The present invention launches radio-frequency front-end, 5GHz receiving radio frequency front ends, 5GHz transmitting radio-frequency front-ends to realize the WLAN radio band signal transactings of entirely different frequency range using independent 2.4GHz receiving radio frequency front ends, 2.4GHz, while supporting WLAN 802.11a/b/g two wave band wireless LAN communications of 2.4GHz and 5GHz.For transmitting, base band is received, the present invention have shared identical ABB and data transformation interface, including channel simulation filter amplifier U35 and U37, analog-digital converter U36 and U38, pulse shaping filter U46 and U48, digital analog converter U47 and U49.
The present invention realizes the support to all four communication pattern frequency translations using single Low Phase Noise Phase-Locked Loop frequency synthesizer B.The channel setup time of phase-locked loop frequency integrator meets the most strict demand of four kinds of communication patterns with phase noise, it is ensured that emission spectrum is with receiving the antijamming capability during signal during output signal.
The advantage of the invention is that：
(1), the present invention supports TD-SCDMA, UHF tri- kinds of communication patterns of RFID, GSM by using same 0.8-2.1GHz wideband orthogonal Direct Conversion structure receiving and transmitting signals path, by making the orthogonal Direct Conversion receiving and transmitting signal paths of the 5GHz Direct Conversion receiving and transmitting signal path orthogonal with the 2.4GHz of WLAN 802.11b/g patterns of WLAN802.11 a patterns fully integrated while supporting WLAN 802.11a/b/g patterns in base band.
(2), by the present invention in that providing local frequency source, reduction system cost of implementation, raising level of integrated system with single Low Phase Noise Phase-Locked Loop frequency synthesizer for all four communication modes.
Brief description of the drawings
Fig. 1 is traditional single mode Direct Conversion wireless transceiver sketch
Fig. 2 is schematic structural view of the invention
Embodiment
Below; will the present invention is described further by specific embodiment; but embodiment is only the citing of alternative embodiment of the present invention, the feature disclosed in it is merely to illustrate and illustrated technical scheme, the protection domain being not intended to limit the present invention.
Refering to Fig. 2, the system architecture and main working process of multi-mode multi-frequency multi-application direct frequency conversion wireless transceiver of the present invention are now described in detail.
Wireless transceiver of the present invention includes 0.8-2.1GHz radio receiving transmitting modules A, the local parts of multimode multi-frequency phase-locked loop frequency integration module B and 2.4/5GHz radio receiving transmitting module C tri-.
0.8-2.1GHz frequency range duplexers U1 in described 0.8-2.1GHz radio receiving transmitting modules A should have been adjusted according to the difference of communication mode, be circulator, be frequency division duplex device in GSM mode in UHF RFID modes.The 0.8-2.1GHz receiving radio frequency front ends low-noise amplifier U3, which realizes the pre-amplification of 0.8-2.1GHz frequency range small-signals using Broadband Matching and broadband structure for amplifying and suppresses rear class 0.8-2.1GHz, receives contributions of the Direct-conversion device U4 to whole wireless receiver noise coefficient, and its noise coefficient and yield value can be respectively 1.5dB and 15dB.The 0.8-2.1GHz receptions Direct-conversion device U4 gives same phase, orthogonal two branch roads and exports to realize that the demodulation to modulation systems such as QPSK is supported.ABB direct current the arrester U5 and U9 are used for eliminating the low-frequency noise contribution of Direct Conversion device, reduce the influence of direct current leakage down coversion, and its high pass angular frequency can be 5kHz.The channel selection filter U6 and U10 can select useful channel signal in strong interference environment, it is ensured that receiver output signal-to-noise ratio in strong interference environment, channel width can be variable in 0.2-1.6MHz.The programmable gain amplifier U7 and U11 is used for realizing the conversion of different received signal levels, meets rear class analog-digital converter U8 and U12 input range requirement, output amplitude can be 1Vpp.TD-SCDMA or UHF RFID base band datas are inputted in the input of the digital analog converter U18 and U21, signal amplitude adjustment is carried out through variable-gain amplifier U17 and U20, the harmonic frequency interference produced when suppressing data conversion through image-rejection filter U16 and U19, realize that zero-frequency, to the direct conversion of radio frequency, the demanded power output that signal power meets different communication modes is amplified through 0.8-2.1GHz transmitting radio-frequency front-ends are usually 30dB variable gain power amplifier U14 through 0.8-2.1GHz transmittings Direct conversion device U15.GSM transmittings data are sent directly into the input IN3 of multi-modulus frequency divider U30 in local multimode multi-frequency phase-locked loop frequency integration module B, voltage controlled oscillator U27 output frequency is controlled with reactance modulation system, frequency values are generally 3-4GHz, and then realize that the modulated signal of covering GSM frequency ranges is exported by the first frequency divider U23 and the second frequency divider U24 frequency dividing effect.
Described local multimode multi-frequency phase-locked loop frequency integration module B uses fractional frequency division frequency synthesis structure, and using multi-modulus frequency divider U30 IN4 ends as the effective control input of frequency dividing ratio, three three bit increments of rank-summation modulator randomization frequency dividing ratio can be used, suppresses phaselocked loop low frequency part phase noise.The 3-4GHz output frequencies of the voltage controlled oscillator U27 are sent to the first frequency divider U23 and the second frequency divider U24 is divided, and meet the frequency needs of three kinds of communication patterns of 0.8-2.1GHz frequency ranges.In addition, the output frequency of the voltage controlled oscillator U27 is also sent to tri-frequency divider U25 and frequency mixer U26 to realize that the frequency of 2.4/5GHz communication patterns is supported.Local multimode multi-frequency phase-locked loop frequency integration module B output end IT1, IT2, IT3, IT4 output difference signal phase noise should be not less than -135dBc/Hz at 1MHz frequency deviations.
Duplexer U31 and U39 in described 2.4/5GHz radio receiving transmitting modules C are time division duplex device.Described 2.4GHz receiving radio frequency front end bandpass filter U32,2.4GHz receiving radio frequency front end low-noise amplifiers U33 and 2.4GHz receives Direct-conversion device U34 and constitutes 2.4GHz receiving radio frequency front ends, described 5GHz receiving radio frequency front end bandpass filter U40,5GHz receiving radio frequency front end low-noise amplifiers U41 and 5GHz receives Direct-conversion device U42 and constitutes 5GHz receiving radio frequency front ends, and the 2.4GHz radiofrequency signals to WLAN802.11b/g and WLAN802.11a 5GHz radiofrequency signals carry out pre-amplification and frequency transformation respectively.Analog filtering the amplifier U35 and U37 of the 10MHz or so bandwidth are used for carrying out Channel assignment and amplitude adjustment, and analog-digital converter U36 and U38 are used for the analogue data of reception being converted into numeral output, used for late-class circuit.Transmitting data are sent in the digital analog converter U47 and U49 inputs IN5, IN6, signal shaping is realized through pulse shaping filter U46 and U48.2.4GHz transmitting radio-frequency front-end bandpass filters U43,2.4GHz transmitting RF front-end power amplifier U44 and 2.4GHz transmitting Direct conversion device U45 constitutes 2.4GHz transmitting radio-frequency front-ends, described 5GHz transmitting radio-frequency front-end bandpass filter U50,5GHz transmitting RF front-end power amplifier U51 and 5GHz transmittings Direct conversion device U52 constitutes 5GHz transmitting radio-frequency front-ends, and WLAN802.11 b/g 2.4GHz radio frequencies modulated signal and WLAN802.11 a 5GHz radio frequencies modulated signal output are realized respectively.
The above enumerates for the specific embodiment of the present invention, for the equipment and structure of wherein not detailed description, it should be understood that take the existing common apparatus in this area and universal method to be practiced.
Claims (1)
1. a kind of multi-mode multi-frequency multi-application direct frequency conversion wireless transceiver, it is characterised in that：The wireless transceiver includes 0.8-2.1GHz radio receiving transmitting modules (A), local multimode multi-frequency phase-locked loop frequency integration module (B) and 2.4/5GHz radio receiving transmitting modules (C), wherein 0.8-2.1GHz radio receiving transmitting modules (A) include 0.8-2.1GHz frequency ranges duplexer (U1) on the receive path, 0.8-2.1GHz receiving radio frequency front ends bandpass filter (U2), 0.8-2.1GHz receiving radio frequency front ends low-noise amplifier (U3), 0.8-2.1GHz receives Direct-conversion device (U4), in-phase channel ABB direct current arrester (U5), in-phase channel selection wave filter (U6), in-phase channel programmable gain amplifier (U7), in-phase channel analog-digital converter (U8), orthogonal channel ABB direct current arrester (U9), orthogonal channel selection wave filter (U10), orthogonal channel programmable gain amplifier (U11), orthogonal channel analog-digital converter (U12)；0.8-2.1GHz radio receiving transmitting modules (A) are on the transmit path comprising 0.8-2.1GHz transmitting radio-frequency front-end bandpass filters (U13), 0.8-2.1GHz transmitting RF front-end power amplifiers (U14), 0.8-2.1GHz transmitting Direct conversion devices (U15), in-phase channel image-rejection filter (U16), in-phase channel variable-gain amplifier (U17), in-phase channel digital analog converter (U18), orthogonal channel image-rejection filter (U19), orthogonal channel variable-gain amplifier (U20), orthogonal channel digital analog converter (U21)；Local multimode multi-frequency phase-locked loop frequency integration module (B) includes variable connector array (U22), the first frequency divider (U23), the second frequency divider (U24), tri-frequency divider (U25), frequency mixer (U26), voltage controlled oscillator (U27), loop filter (U28), Frequency/Phase Discriminator (U29), multi-modulus frequency divider (U30)；2.4/5GHz radio receiving transmitting modules (C) receive Direct-conversion device (U34) on 2.4GHz RX paths comprising 2.4GHz duplexers (U31), 2.4GHz receiving radio frequency front ends bandpass filter (U32), 2.4GHz receiving radio frequency front ends low-noise amplifier (U33), 2.4GHz；2.4/5GHz radio receiving transmitting modules (C) are receiving base band shared in-phase channel analog filtering amplifier (U35), in-phase channel analog-digital converter (U36), orthogonal channel analog filtering amplifier (U37), orthogonal channel analog-digital converter (U38)；2.4/5GHz radio receiving transmitting modules (C) receive Direct-conversion device (U42) on 5GHz RX paths comprising 5GHz duplexers (U39), 5GHz receiving radio frequency front ends bandpass filter (U40), 5GHz receiving radio frequency front ends low-noise amplifier (U41), 5GHz；2.4/5GHz radio receiving transmitting modules (C) include 2.4GHz transmitting radio-frequency front-end bandpass filters (U43), 2.4GHz transmitting RF front-end power amplifiers (U44), 2.4GHz transmitting Direct conversion devices (U45) on 2.4GHz transmission paths；2.4/5GHz radio receiving transmitting modules (C) share in-phase channel pulse shaping filter (U46), in-phase channel digital analog converter (U47), orthogonal channel pulse shaping filter (U48), orthogonal channel digital analog converter (U49) in transmitting baseband；2.4/5GHz radio receiving transmitting modules (C) include 5GHz transmitting radio-frequency front-end bandpass filters (U50), 5GHz transmitting RF front-end power amplifiers (U51), 5GHz transmitting Direct conversion devices (U52) on 5GHz transmission paths；The 0.8-2.1GHz frequency ranges duplexer (U1) has a bidirectional end RF1 to be connected with exterior antenna, one output end is connected with the input of 0.8-2.1GHz receiving radio frequency front ends bandpass filter (U2), and an input is connected with the 0.8-2.1GHz output ends for launching radio-frequency front-end bandpass filter (U13)；The output end of the 0.8-2.1GHz receiving radio frequency front ends bandpass filter (U2) is connected with the input of 0.8-2.1GHz receiving radio frequency front ends low-noise amplifier (U3)；The difference output end of the 0.8-2.1GHz receiving radio frequency front ends low-noise amplifier (U3) is connected with the 0.8-2.1GHz differential input ends for receiving Direct-conversion device (U4)；The 0.8-2.1GHz, which receives Direct-conversion device (U4), has one to be connected with phase difference output end with the differential input end of in-phase channel ABB direct current arrester (U5), and an orthogonal differential output end is connected with the differential input end of orthogonal channel ABB direct current arrester (U9)；The difference output end of the in-phase channel ABB direct current arrester (U5) selects the differential input end of wave filter (U6) to be connected with in-phase channel；The difference output end of the in-phase channel selection wave filter (U6) is connected with the differential input end of in-phase channel programmable gain amplifier (U7)；The difference output end of the in-phase channel programmable gain amplifier (U7) is connected with the differential input end of in-phase channel analog-digital converter (U8)；The data terminal output end of the in-phase channel analog-digital converter (U8) is OUT1；The difference output end of the orthogonal channel ABB direct current arrester (U9) selects the Differential Input of wave filter (U10) to be connected with orthogonal channel；The difference output end of the orthogonal channel selection wave filter (U10) is connected with the differential input end of orthogonal channel programmable gain amplifier (U11)；The difference output end of the orthogonal channel programmable gain amplifier (U11) is connected with the differential input end of orthogonal channel analog-digital converter (U12)；The data terminal output end of the orthogonal channel analog-digital converter (U12) is OUT2；The input of the 0.8-2.1GHz transmitting radio-frequency front-end bandpass filters (U13) is connected with the 0.8-2.1GHz output ends for launching RF front-end power amplifier (U14)；The differential input end of the 0.8-2.1GHz transmitting RF front-end power amplifiers (U14) is connected with difference output end IT2, IT2B of the 0.8-2.1GHz difference output ends and variable connector array (U22) for launching Direct conversion device (U15)；The same phase differential input end of the 0.8-2.1GHz transmitting Direct conversion devices (U15) is connected with the difference output end of in-phase channel image-rejection filter (U16), and its orthogonal differential input is connected with the difference output end of orthogonal channel image-rejection filter (U19)；The differential input end of the in-phase channel image-rejection filter (U16) is connected with the difference output end of in-phase channel variable-gain amplifier (U17)；The differential input end of the in-phase channel variable-gain amplifier (U17) is connected with the difference output end of in-phase channel digital analog converter (U18)；The data input pin of the in-phase channel digital analog converter (U18) is IN1；The differential input end of the orthogonal channel image-rejection filter (U19) is connected with the difference output end of orthogonal channel variable-gain amplifier (U20)；The differential input end of the orthogonal channel variable-gain amplifier (U20) is connected with the difference output end of orthogonal channel digital analog converter (U21)；The data input pin of the orthogonal channel digital analog converter (U21) is IN2；Difference output end IT1, IT1B of the variable connector array (U22) are connected with the 0.8-2.1GHz local oscillator differential input ends for receiving Direct-conversion device (U4) and 0.8-2.1GHz transmitting Direct conversion devices (U15)；Difference output end of two differential input ends of the variable connector array respectively with the first frequency divider (U23) and the second frequency divider (U24) is connected；The input of first frequency divider (U23) is connected with the positive output end of the second frequency divider (U24)；The input of second frequency divider (U24) is connected with the output end of voltage controlled oscillator (U27)；The frequency mixer (U26) is using the Single-end output of the difference output of the second frequency divider (U24) and voltage controlled oscillator (U27) as input, its difference output end is IT4, IT4B, while being connected with the differential input end of tri-frequency divider (U25)；The difference output end of the tri-frequency divider (U25) is IT3, IT3B；The input of the voltage controlled oscillator (U27) is connected with the output end of loop filter (U28), and output end is connected with an input of multi-modulus frequency divider (U30)；The input of the loop filter (U28) is connected with the output end of Frequency/Phase Discriminator (U29)；The input of the Frequency/Phase Discriminator (U29) is connected with the output end of multi-modulus frequency divider (U30)；Two other input of the multi-modulus frequency divider (U30) is IN3, IN4, is respectively intended to input increment-summation modulator data and global system for mobile telecommunications (GSM) transmitting data；The 2.4GHz duplexers (U31) have a bidirectional end RF2 to be connected with exterior antenna, one output end is connected with the input of 2.4GHz receiving radio frequency front ends bandpass filter (U32), and an input is connected with the 2.4GHz output ends for launching radio-frequency front-end bandpass filter (U43)；The output end of the 2.4GHz receiving radio frequency front ends bandpass filter (U32) is connected with the input of 2.4GHz receiving radio frequency front ends low-noise amplifier (U33)；The difference output end of the 2.4GHz receiving radio frequency front ends low-noise amplifier (U33) is connected with the 2.4GHz differential input ends for receiving Direct-conversion device (U34)；The 2.4GHz, which receives Direct-conversion device (U34), has one to be connected with phase difference output end with the differential input end of in-phase channel analog filtering amplifier (U35), and an orthogonal differential output end is connected with the differential input end of orthogonal channel analog filtering amplifier (U37)；The difference output end of the in-phase channel analog filtering amplifier (U35) is connected with the Differential Input of in-phase channel analog-digital converter (U36)；The data output end of the in-phase channel analog-digital converter (U36) is OUT3；The difference output end of the orthogonal channel analog filtering amplifier (U37) is connected with the Differential Input of orthogonal channel analog-digital converter (U38)；The data output end of the orthogonal channel analog-digital converter (U38) is OUT4；The input of the 2.4GHz transmitting radio-frequency front-end bandpass filters (U43) is connected with the 2.4GHz output ends for launching RF front-end power amplifier (U44)；The differential input end of the 2.4GHz transmitting RF front-end power amplifiers (U44) is connected with the 2.4GHz difference output ends for launching Direct conversion device (U45)；The same phase Differential Input of the 2.4GHz transmitting Direct conversion devices (U45) is connected with the difference output end of in-phase channel pulse shaping filter (U46), and orthogonal differential input is connected with the difference output end of orthogonal channel pulse shaping filter (U48)；The 2.4GHz receives Direct-conversion device (U34) and the local oscillator differential input end of 2.4GHz transmitting Direct conversion devices (U45) is IT3, IT3B；The differential input end of the in-phase channel pulse shaping filter (U46) is connected with the difference output end of in-phase channel digital analog converter (U47)；The data input pin of the in-phase channel digital analog converter (U47) is IN5；The differential input end of the orthogonal channel pulse shaping filter (U48) is connected with the difference output end of orthogonal channel digital analog converter (U49)；The data input pin of the orthogonal channel digital analog converter (U49) is IN6；The 5GHz duplexers (U39) have a bidirectional end RF3 to be connected with exterior antenna, one output end is connected with the input of 5GHz receiving radio frequency front ends bandpass filter (U40), and an input is connected with the 5GHz output ends for launching radio-frequency front-end bandpass filter (U50)；The output end of the 5GHz receiving radio frequency front ends bandpass filter (U40) is connected with the input of 5GHz receiving radio frequency front ends low-noise amplifier (U41)；The difference output end of the 5GHz receiving radio frequency front ends low-noise amplifier (U41) is connected with the 5GHz differential input ends for receiving Direct-conversion device (U42)；The 5GHz, which receives Direct-conversion device (U42), has one to be connected with phase difference output end with the differential input end of in-phase channel analog filtering amplifier (U35), and an orthogonal differential output end is connected with the differential input end of orthogonal channel analog filtering amplifier (U37)；The input of the 5GHz transmitting radio-frequency front-end bandpass filters (U50) is connected with the 5GHz output ends for launching RF front-end power amplifier (U51)；The differential input end of the 5GHz transmitting RF front-end power amplifiers (U51) is connected with the 5GHz difference output ends for launching Direct conversion device (U52)；The same phase Differential Input of 5GHz transmitting Direct conversion devices (U52) is connected with the difference output end of in-phase channel pulse shaping filter (U46), and orthogonal differential input is connected with the difference output end of orthogonal channel pulse shaping filter (U48)；The 5GHz receives Direct-conversion device (U42) and the local oscillator differential input end of 5GHz transmitting Direct conversion devices (U52) is IT4, IT4B.
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| CN104112108A (en) * | 2014-06-30 | 2014-10-22 | 广西瀚特信息产业股份有限公司 | Multi-frequency band RFID reading device and method |
| CN104617966A (en) * | 2014-12-31 | 2015-05-13 | 杭州敦崇科技股份有限公司 | WLAN (wireless local area network) adjacent channel interference resisting device and method thereof |
| CN106301362A (en) * | 2016-08-01 | 2017-01-04 | 广东美的厨房电器制造有限公司 | Source signal generating means and microwave oven |
| WO2017071331A1 (en) * | 2015-10-27 | 2017-05-04 | 中兴通讯股份有限公司 | Multi-frequency band transceiver, and method for transmitting and receiving multi-frequency band radio-frequency signal |
| CN106849984A (en) * | 2017-02-20 | 2017-06-13 | 广州海格通信集团股份有限公司 | A kind of shared method and system of multi-mode radio frequency |
| CN107690752A (en) * | 2014-11-25 | 2018-02-13 | 株式会社Kmw | The synthesizer and synthesizer control method used in multiband base station system |
| CN107769814A (en) * | 2017-09-26 | 2018-03-06 | 广东欧珀移动通信有限公司 | Lift circuit, mobile terminal and the signal processing method of main collection receiving sensitivity |
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| CN113660004A (en) * | 2021-08-19 | 2021-11-16 | 中国电子科技集团公司第三十八研究所 | Multimode multiplexing transceiving front-end circuit and control method |
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| CN102075208B (en) * | 2010-12-31 | 2013-07-31 | 东南大学 | Radio frequency front-end with low power consumption |
| CN102075208A (en) * | 2010-12-31 | 2011-05-25 | 东南大学 | Radio frequency front-end with low power consumption |
| CN102664653A (en) * | 2012-05-17 | 2012-09-12 | 天津里外科技有限公司 | Mobile terminal and radio frequency front terminal thereof with radio frequency digital-to-analog conversion type linear transmitter |
| CN102664653B (en) * | 2012-05-17 | 2014-09-03 | 天津里外科技有限公司 | Mobile terminal and radio frequency front terminal thereof with radio frequency digital-to-analog conversion type linear transmitter |
| CN104112108A (en) * | 2014-06-30 | 2014-10-22 | 广西瀚特信息产业股份有限公司 | Multi-frequency band RFID reading device and method |
| CN107690752A (en) * | 2014-11-25 | 2018-02-13 | 株式会社Kmw | The synthesizer and synthesizer control method used in multiband base station system |
| CN107690752B (en) * | 2014-11-25 | 2019-12-27 | 株式会社Kmw | Synthesizer used in multi-band base station system and synthesizer control method |
| CN104617966A (en) * | 2014-12-31 | 2015-05-13 | 杭州敦崇科技股份有限公司 | WLAN (wireless local area network) adjacent channel interference resisting device and method thereof |
| WO2017071331A1 (en) * | 2015-10-27 | 2017-05-04 | 中兴通讯股份有限公司 | Multi-frequency band transceiver, and method for transmitting and receiving multi-frequency band radio-frequency signal |
| CN106301362B (en) * | 2016-08-01 | 2019-04-23 | 广东美的厨房电器制造有限公司 | Source signal generating device and micro-wave oven |
| CN106301362A (en) * | 2016-08-01 | 2017-01-04 | 广东美的厨房电器制造有限公司 | Source signal generating means and microwave oven |
| CN106849984A (en) * | 2017-02-20 | 2017-06-13 | 广州海格通信集团股份有限公司 | A kind of shared method and system of multi-mode radio frequency |
| CN107769814A (en) * | 2017-09-26 | 2018-03-06 | 广东欧珀移动通信有限公司 | Lift circuit, mobile terminal and the signal processing method of main collection receiving sensitivity |
| CN109212487A (en) * | 2018-09-27 | 2019-01-15 | 芜湖博高光电科技股份有限公司 | A kind of TR component of two-band one |
| CN110045343A (en) * | 2019-05-10 | 2019-07-23 | 南京新频点电子科技有限公司 | A kind of broad-band multipath radar signal synthetic simulation environment and its working method |
| CN113660004A (en) * | 2021-08-19 | 2021-11-16 | 中国电子科技集团公司第三十八研究所 | Multimode multiplexing transceiving front-end circuit and control method |
| CN113660004B (en) * | 2021-08-19 | 2022-05-20 | 中国电子科技集团公司第三十八研究所 | Multimode multiplexing transceiving front-end circuit and control method |
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