CN101883464B - Current follow-up passive factor correction circuit and electronic ballast starting circuit - Google Patents
Current follow-up passive factor correction circuit and electronic ballast starting circuit Download PDFInfo
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- CN101883464B CN101883464B CN201010191174.2A CN201010191174A CN101883464B CN 101883464 B CN101883464 B CN 101883464B CN 201010191174 A CN201010191174 A CN 201010191174A CN 101883464 B CN101883464 B CN 101883464B
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Abstract
The invention is applied to the fields of circuits and provides a current follow-up passive factor correction circuit and an electronic ballast starting circuit. A current follow-up circuit in the current follow-up passive factor correction circuit comprises diodes VD21, VD22, VD23 and VD24 connected in series in turn, a capacitor C1, a capacitor C2, and a high-frequency filter capacitor CV. An anode of the diode VD21 is grounded; and a cathode of the diode VD24 is connected with a post-stage resonant conversion driving circuit. One end of the capacitor C1 is connected with a common cathode of a bridge rectifier circuit and the other end of the capacitor C1 is connected with a junction between the diodes VD21 and VD22. One end of the capacitor C2 is connected with a junction between the diodes VD23 and VD22 and the other end of the capacitor C2 is grounded. One end of the high-frequency filter capacitor CV is connected with the junction between the diodes VD22 and VD23 and the other end of the high-frequency filter capacitor CV is connected with the post-stage resonant conversion driving circuit. The current follow-up passive factor correction circuit can effectively improve an output voltage waveform and obviously reduce a THD value.
Description
Technical field
The invention belongs to circuit field, relate in particular to a kind of by stream passive factor correction circuit and electronic ballast starting circuit.
Background technology
Traditional current follow-up circuit is owing to being subject to the restriction of operation principle and circuit structure, output dc voltage ripple composition is larger, the voltage ratio of direct current peak dot and valley point was close to 2: 1, although the direct voltage of fluctuation does not have too much influence to the normal work of electric ballast, but the lamp current crest factor to electric ballast output has considerable influence, therefore in the time adopting current follow-up circuit, must be noted that the control to output lamp current crest factor, make it meet the requirement of related standards.
The bridge full-wave rectifier ohmic load circuit of employing current follow-up circuit as shown in Figure 1, is wherein basic current follow-up circuit in square frame, and its basic principle is:
In the time of t < 0, current follow-up circuit, in initial condition, does not all have voltage, Vo=0 on capacitor C 1, C2.
In the time of t=0, connect the mains switch of AC-input voltage Vin, and hypothesis is just now the leading zero's of the positive half cycle of Vin.
During 0 < t < 5ms, AC-input voltage
progressively increase from zero to Vm direction with sinusoidal rule.The now reverse-biased cut-off of rectifier diode VD2, VD4, rectifier diode VD1, VD3 forward conduction, the series loop charging that AC-input voltage Vin consists of to capacitor C 1, diode VD6, capacitor C 2 diode VD1, VD3 provides electric current to load RL simultaneously.
Due to the internal resistance sum (3r of rectifier diode VD1, VD3, VD6 and input power Vin now
d+ r
in) very little, charge circuit electric capacity
also less, charge constant τ is:
Due to charge constant, τ is very little, so the Vo of the output voltage of current follow-up circuit is chasing AC-input voltage Vin to rise.In the time that Vin rises to peak value Vm (approximately 311), Vo is also almost charged to peak value Vm, at this moment Vc1 ≈ Vc2 ≈ Vm/2 simultaneously.
In the time of t>=5ms, input voltage is pressed sinusoidal rule from peak value Vm
start to decline.Concerning common rectification circuit, rectifier diode VD1, VD3 will reverse-biasedly end, but current follow-up circuit is different.In the time that AC-input voltage Vin starts to decline from Vm, capacitor C 1 will be discharged by load RL, diode VD7.Once diode VD7 conducting, Vo presses exponential law and changes:
So during this period of time, AC-input voltage Vin is high than Vo in each moment.Whenever AC-input voltage Vin declines in a flash from Vm, capacitor C 1 is just rapidly by load RL, diode VD7 electric discharge, and its discharge rate is higher than sinusoidal fall off rate.Until the Vin=Vm/2 moment, the voltage Vm/2 at capacitor C 1 two ends is down to zero because of electric discharge.In the time of Vin < Vm/2, diode VD5 is by automatic conducting, and in capacitor C 2, the electric charge of storage will pass through rapidly diode VD5, load RL electric discharge, give load afterflow.After this, occur Vin < Vo state, so rectifier diode VD1, VD3 start cut-off, capacitor C 2 is discharged with exponential law by diode VD5, load RL always.During this period, Vo changes with exponential law.
After t >=10ms, Vin is in negative half period, the now reverse-biased cut-off of rectifier diode VD1, VD3, and rectifier diode VD2, VD4 be now also in reverse-biased, conducting at once.
During 10ms < t < 15ms, to wait until when input voltage is greater than output voltage always, just conducting of rectifier diode VD2, VD4, power supply Vin charges first to capacitor C 1 by capacitor C 1, diode VD6, capacitor C 2.In like manner, because charge constant τ is very little, charge very fast, Vo reaches rapidly Vin instantaneous value at this moment, and then Vin continues to charge to capacitor C 1 on the one hand, electric current is provided on the other hand load RL.Because capacitor C 1 is charged, its current potential rises to the voltage Vc2 (min) equaling in capacitor C 2, the continuation of Vin is risen and will be transferred to by capacitor C 1, diode VD6, capacitor C 2 serial connection charge simultaneously, the current potential at capacitor C 1, C2 two ends starts to rise from Vo (min) simultaneously, now, Vo will chase again Vin and rise with sinusoidal rule.In the time that input voltage vin rises to crest voltage Vm, VC1, VD6, tri-voltage sums of VC2 rise to rapidly Vm, at this moment get back to again Vc1 ≈ Vc2 ≈ Vm/2 state.
After this will go round and begin again, form DC pulse moving voltage Vo at load RL two ends.It is no longer spike pulse that current follow-up circuit makes the waveform of source current, the harmonic components being caused by pulse current reduces, but progressively trend is continuous, its current amplitude also greatly reduces, the ON time of rectifier diode increases simultaneously, but to output voltage waveforms to improve effect undesirable, can not effectively solve because input current spike causes the too high problem of THD value.
Summary of the invention
The object of the embodiment of the present invention is to provide a kind of can effectively improve output voltage waveforms by stream passive factor correction circuit, obviously reduces the THD value causing due to input current spike.
The embodiment of the present invention is achieved in that one, by stream passive factor correction circuit, comprises bridge rectifier, and current follow-up circuit, and described current follow-up circuit comprises:
Diode VD21, VD22, VD23 and the VD24 of series connection successively, the plus earth of described diode VD21, the negative electrode of described diode VD24 connects rear class resonant transformation drive circuit;
Capacitor C 2, its one end connects the contact in the middle of described diode VD23, VD22, other end ground connection; And
High-frequency filter capacitor CV, its one end connects the contact in the middle of described diode VD22, VD23, and the other end connects rear class resonant transformation drive circuit.
Another object of the embodiment of the present invention is to provide a kind of electronic ballast starting circuit, and described start-up circuit comprises:
High-frequency filter circuit, for carrying out High frequency filter to exchanging input, eliminates High-frequency Interference;
Bridge rectifier, for carrying out rectification to the alternating current after described high-frequency filter circuit High frequency filter, output ripple direct current;
Current follow-up circuit, proofreaies and correct for the power factor to described pulsating direct current, suppresses input current spike composition; And
Resonant transformation drive circuit, for further eliminating the humorous wave interference of described pulsating direct current, drives rear class load;
Described current follow-up circuit comprises:
Diode D8, D7, D6 and the D5 of series connection successively, the anode of described diode D8 connects described resonant transformation drive circuit, and the negative electrode of described diode D5 connects the common cathode limit of described bridge rectifier;
Capacitor C 8, its one end connects the contact in the middle of described diode D7, D8, and the other end connects described resonant transformation drive circuit;
Capacitor C 9, its one end connects the common anode limit of described bridge rectifier, and the other end connects the contact in the middle of described diode D5, D6; And
High-frequency filter capacitor, one end connects the contact of described diode D6, D7, and the other end connects described resonant transformation drive circuit.
Another object of the embodiment of the present invention is to provide a kind of electric ballast, comprises start-up circuit, and described start-up circuit comprises:
High-frequency filter circuit, for carrying out High frequency filter to exchanging input, eliminates High-frequency Interference;
Bridge rectifier, for carrying out rectification to the alternating current after described high-frequency filter circuit High frequency filter, output ripple direct current;
Current follow-up circuit, proofreaies and correct for the power factor to described pulsating direct current, suppresses input current spike composition; And
Resonant transformation drive circuit, for further eliminating the humorous wave interference of described pulsating direct current, drives rear class load;
Described current follow-up circuit comprises:
Diode D8, D7, D6 and the D5 of series connection successively, the anode of described diode D8 connects described resonant transformation drive circuit, and the negative electrode of described diode D5 connects the common cathode limit of described bridge rectifier;
Capacitor C 8, its one end connects the contact in the middle of described diode D7, D8, and the other end connects described resonant transformation drive circuit;
Capacitor C 9, its one end connects the common anode limit of described bridge rectifier, and the other end connects the contact in the middle of described diode D5, D6; And
High-frequency filter capacitor, one end connects the contact of described diode D6, D7, and the other end connects described resonant transformation drive circuit.
Another object of the embodiment of the present invention is to provide a kind of lighting apparatus that comprises above-mentioned electric ballast.
The embodiment of the present invention is by splitting into a diode between electric capacity in traditional current follow-up circuit two diode series connection, and at two diodes and the middle high-frequency filter capacitor that adds of rear class resonant transformation drive circuit, can effectively improve output voltage waveforms, obviously reduce the THD value causing due to input current spike, and can effectively improve the power factor of electric ballast, harmonic reduction current interference.
Accompanying drawing explanation
Fig. 1 is the structure chart of the bridge full-wave rectifier ohmic load circuit of the employing current follow-up circuit that provides of prior art;
Fig. 2 is the structure chart of the current follow-up circuit that provides of the embodiment of the present invention;
Fig. 3 is the circuit theory diagrams of the electronic ballast starting circuit that provides of the embodiment of the present invention;
Fig. 4 is the structure chart of the electronic ballast starting circuit medium-high frequency filter circuit that provides of the embodiment of the present invention;
Fig. 5 is the structure chart of bridge-type rectified current in the electronic ballast starting circuit that provides of the embodiment of the present invention;
Fig. 6 is the structure chart of current follow-up circuit in the electronic ballast starting circuit that provides of the embodiment of the present invention;
Fig. 7 is the structure chart of resonant transformation drive circuit in the electronic ballast starting circuit that provides of the embodiment of the present invention.
Embodiment
In order to make object of the present invention, technical scheme and advantage clearer, below in conjunction with drawings and Examples, the present invention is further elaborated.Should be appreciated that specific embodiment described herein, only in order to explain the present invention, is not intended to limit the present invention.
The diode that the embodiment of the present invention is come traditional current follow-up circuit Central Plains between electric capacity splits into two diode series connection, and add high-frequency filter capacitor in the middle of two diodes and rear class resonant transformation drive circuit, make can effectively improve by stream Passive Power factor correction circuit power factor and the harmonic reduction current interference of electric ballast.
Fig. 2 shows the structure by stream passive factor correction circuit that the embodiment of the present invention provides, and for convenience of explanation, only shows the part relevant to the embodiment of the present invention.
Bridge rectifier 2 is made up of four rectifier diode VD1～VD4, and four rectifier diodes are connected into electric bridge form, therefore claim bridge rectifier.In the time of the positive half cycle of alternating current VSIN, rectifier diode VD1, VD3 conducting, rectifier diode VD2, VD4 cut-off, the lower end that electric current is got back to filter circuit 1 by the upper end of filter circuit 1 through rectifier diode VD1 → current follow-up circuit 3 → rectifier diode VD3 obtains a half-wave commutating voltage on current follow-up circuit 3.
At the negative half period of alternating current VSIN, rectifier diode VD1, VD3 cut-off, rectifier diode VD2, VD4 conducting, electric current is got back to filter circuit 1 upper end by the lower end of filter circuit 1 through VD2 → current follow-up circuit 3 → VD4, obtains another half-wave commutating voltage on current follow-up circuit 3.
Like this, just on current follow-up circuit 3, obtain a voltage waveform identical with full-wave rectification, the calculating of its electric current is identical with full-wave rectification.
Current follow-up circuit 3 comprises capacitor C 1, C2, diode VD21, VD22, VD23 and VD24, and high-frequency filter capacitor Cv.Wherein:
Diode VD21, VD22, VD23 and VD24 connect successively, the plus earth of diode VD21, and the negative electrode of diode VD24 connects rear class resonant transformation drive circuit.
One end of capacitor C 1 connects the common cathode limit of bridge rectifier 2, and the other end connects the contact in the middle of diode VD21, VD22.
One end of capacitor C 2 connects the contact in the middle of diode VD23, VD22, other end ground connection.
A terminating diode VD23 of high-frequency filter capacitor Cv and the contact of VD22, the other end connects rear class resonant transformation drive circuit.
In the time that input voltage changes from zero toward peak value Vm with sinusoidal rule, the series loop charging that capacitor C 1, diode VD22, VD23 and capacitor C 2 form provides electric current to load simultaneously.
When input voltage starts to decline from peak value Vm, capacitor C 1 is by load and diode VD21 electric discharge.
In the time that capacitor C 1 both end voltage is down to zero, the automatic conducting of diode VD24, capacitor C 2, by load and diode VD24 electric discharge, is given load afterflow.
When input voltage is in negative half period, when input voltage is greater than output voltage, power supply charges to the series loop being made up of capacitor C 1, C2 and diode VD21, VD22, and output voltage is followed input voltage and risen.
In the time that input voltage rises to peak value Vm, get back to again original state, thus the direct voltage of pulsing in load two ends form, diode VD21, VD22 can reduce the peak current in reciprocal charging process.
From the above, in current follow-up circuit 3, the embodiment of the present invention is by splitting into a diode between capacitor C 1, C2 in existing current follow-up circuit VD21, two diode series connection of VD22, and at two diode VD21, VD22 and the middle high-frequency filter capacitor Cv that adds of rear class resonant transformation drive circuit, every half period in electric main input is charged to capacitor C 1, C2, and each electric capacity is charged to
and 4 diode drops that deduct (two diodes in bridge rectifier 2 and diode VD22, VD21).
In embodiments of the present invention, diode volume resistance R
vD22, R
vD23can effectively reduce the peak current in capacitor C 1, the reciprocal charging process of C2.Typical is the principal element that causes THD value larger by the spike in the input current Iin of streaming electric ballast, this embodiment of the present invention is added to high-frequency filter capacitor Cv between by stream power factor correction stage and rear class resonant transformation, high-frequency filter capacitor Cv charges to capacitor C 1, C2 according to the direction of high-frequency resonant inverter current, thereby make voltage on capacitor C 1, the C2 half higher than input voltage peak value Vm, the voltage valley of DC bus is greater than
after improving, output voltage waveforms is improved greatly, and THD value obviously reduces.
The embodiment of the present invention can be applied in the electric ballast of various lighting apparatus, and Fig. 3 shows the structure of the electronic ballast starting circuit that the embodiment of the present invention provides, and only shows for convenience of explanation the part relevant to the embodiment of the present invention.
High-frequency filter circuit 31 carries out High frequency filter to electric main input, eliminates High-frequency Interference, exports bridge rectifier 32 to.
The alternating current of bridge rectifier 32 after to high-frequency filter circuit 31 High frequency filters carries out rectification, output ripple direct current.
The power factor of the pulsating direct current that current follow-up circuit 33 is exported bridge rectifier 32 is proofreaied and correct, and suppresses input current spike composition, and harmonic reduction electric current can effectively improve the power factor of electric ballast, harmonic reduction current interference.
The harmonic carcellation that resonant transformation drive circuit 34 is further eliminated pulsating direct current disturbs, and drives rear class load circuit, as electric ballast.
As shown in Figure 4, high-frequency filter circuit 31 is two π type LC high-frequency filter circuits, comprises capacitor C 1～C7, inductance L 1～L4.
Exchange the π type lc circuit that input first forms through inductance L 1, capacitor C 1, C2, pass through again inductance L 2, L3, two π type lc circuits of capacitor C 3, C4 composition, then pass through inductance L 4, the π type lc circuit of capacitor C 4, C5 composition, finally will capacitor C 6, be incorporated to circuit after C7 serial connection, the tie point ground connection of capacitor C 6 and C7.
The π type lc circuit that interchange input forms through capacitor C 1, C2 and inductance L 1 carries out High frequency filter, eliminate the harmonious wave interference of high fdrequency component in exchanging, its output is carried out filtering through inductance L 2, L3, and then the π type lc circuit forming through capacitor C 4, C5 and inductance L 4 carries out High frequency filter, eliminate High-frequency Interference finally by capacitor C 6, C7, after multistage High frequency filter, the alternating current after output improves.
As shown in Figure 5, Figure 6, bridge rectifier 32 comprises the bridge rectifier of four diode D1, D2, D3 and D4 composition, wherein:
The common cathode limit of bridge rectifier connects the negative electrode of diode D5 in current follow-up circuit 33, and common anode limit connects the negative pole of capacitor C 9 in current follow-up circuit 33.
The anode of diode D3 is connected with the ungrounded end of capacitor C 6 in high-frequency filter circuit 31.
The negative electrode of diode D2 is connected with the ungrounded end of capacitor C 7 in high-frequency filter circuit 31.
The interchange input rectifying that bridge rectifier 32 is exported high-frequency filter circuit 31 becomes direct current output.Exchange input in the time of positive half period, diode D2, D3 conducting, D1, D4 turn-off, 3. end is for just, 4. end, for negative, exchanges input in the time of negative half-cycle, diode D1, D4 conducting, D2, D3 turn-off, now, 3. end, still for just, is 4. held still for negative, be output as direct current, exchange input rectifying and become direct current output.
When interchange is input as timing, 1. end, for just, is 2. held as bearing, and diode D2, D3 bear forward voltage conducting, and diode D1, D4 bear reverse voltage and turn-off, and electric current flows out from diode D3, and from diode D2 inflow, now, 3. end, for just, is 4. held as negative.
When interchange is input as when negative, 1. end is for negative, and 2. end is for just, and diode D1, D4 bear forward voltage conducting, and diode D2, D3 bear reverse voltage and turn-off, and electric current flows out from diode D1, flows into from diode D4, and now, 3. end is for just, and 4. end is to bear.As can be seen here, 3. end is just always, and 4. end is always negative, and the interchange input that high-frequency filter circuit 31 is exported becomes the direct current output of pulsation.
Current follow-up circuit 33 adopts the improvement structure of the embodiment of the present invention, and as shown in Figure 6, capacitor C 10, C11 parallel connection, be equivalent to the high-frequency filter capacitor Cv in Fig. 2, wherein:
Diode D8, D7, D6 and D5 connect successively, and the anode of diode D6 connects resonant transformation drive circuit 34, and the negative electrode of diode D5 connects the common cathode limit of bridge rectifier 32.
One end of capacitor C 8 connects the contact in the middle of diode D7, D8, and the other end connects resonant transformation drive circuit 34.
One end of capacitor C 9 connects the common anode limit of bridge rectifier 32, and the other end connects the contact in the middle of diode D5, D6.
One end of high-frequency filter capacitor connects the contact of diode D6, D7, and the other end connects resonant transform circuit 34, charges to capacitor C 8, C9 according to the direction of high-frequency resonant inverter current.
As one embodiment of the present of invention, original high-frequency filter capacitor is divided into two capacitor C 10, C11, one end of capacitor C 10 connects the contact of diode D6, D7, and the other end connects one end of resonant transformation drive circuit 34; One end of capacitor C 11 connects the contact of diode D6, D7, and the other end connects the other end of resonant transformation drive circuit 34.
In embodiments of the present invention, capacitor C 8, C9 can adopt electrochemical capacitor.
In the time that input voltage changes from zero toward peak value Vm with sinusoidal rule, the series loop charging that capacitor C 8, diode D7, D6 and capacitor C 9 form provides electric current to load simultaneously.
When input voltage starts to decline from peak value Vm, capacitor C 8 is discharged by load and diode D8, in the time that capacitor C 8 both end voltage are down to zero, and the automatic conducting of diode D5, capacitor C 9, by load and diode D5 electric discharge, is given load afterflow.
When input voltage is in negative half period, when input voltage is greater than output voltage, the series loop being made up of capacitor C 8, diode D7, D6 and capacitor C 9 is charged, and output voltage is followed input voltage and risen.
In the time that input voltage rises to peak value Vm, get back to again original state, thus the direct voltage of pulsing in load two ends form, diode D6, D7 can reduce the peak current in reciprocal charging process.
The rear connecting electronic ballast of resonant transformation drive circuit 34, as shown in Figure 7, resonant transformation drive circuit 34 comprises diode D9～D13, resistance R 1～R6, capacitor C 12, C13, inductance L 5～L9, NPN triode Q1, Q2 and bi-directional voltage stabilizing pipe DB.
The negative electrode of diode D9 is connected with the positive pole of capacitor C 8 in current follow-up circuit 33, and anode is connected with the negative electrode of diode D10, and the anode of diode D10 is connected with the anode of diode D8 in current follow-up circuit 33.
One end of resistance R 1 is connected with the negative electrode of diode D9, and the other end is connected with the anode of diode D9.
One end of capacitor C 12 is connected with the negative electrode of diode D9, and the other end is connected with the anode of diode D9.
The collector electrode of NPN triode Q1 is connected with the negative electrode of diode D9, and emitter is connected with one end of resistance R 2, and the other end of resistance R 2 is connected with the collector electrode of NPN triode Q2.
The emitter of NPN triode Q2 is connected with one end of resistance R 6, the other end of resistance R 6 is connected with the anode of diode D10, the base stage of NPN triode Q1 is connected with resistance R 4, and the other end of resistance R 4 is connected with one end of inductance L 5, and the other end of inductance L 5 is connected with the negative electrode of diode D11.
Diode D11 anode is connected with one end of inductance L 6, and the other end of inductance L 6 is connected with the anode of diode D10.
The base stage of NPN triode Q2 is connected with one end of resistance R 5, and the other end of resistance R 5 is connected with the anode of diode D11.
One end of capacitor C 13 is connected with the anode of diode D11, and the other end is connected with the anode of diode D10.
One end of bi-directional voltage stabilizing pipe DB is connected with the base stage of NPN triode Q2, and the other end is connected with the anode of diode D11.
One end of resistance R 3 is connected with the negative electrode of diode D9, and the other end is connected with the anode of diode D11.
One end of inductance L 7 is connected with the anode of diode D9, and the other end is connected with one end of inductance L 8, and inductance L 8 other ends are connected with one end of inductance L 9, and inductance L 9 other ends are connected with the anode of diode D13.
The anode of diode D12 is connected with the anode of diode D6 in current follow-up circuit 33.
In the electronic ballast starting circuit providing in the embodiment of the present invention, exchange input and enter high-frequency filter circuit 31, electric capacity in high-frequency filter circuit 31 is eliminated the high fdrequency component in input, inductance carries out filtering to input, harmonic carcellation disturbs, and exports bridge rectifier 32 to, through the rectifier bridge of four diode compositions, each moment, different brachium pontis respectively had a diode current flow up and down, realized the rectification to exchanging input.
The pulsating direct current that bridge rectifier 32 is exported is to current follow-up circuit 33, when voltage is during from zero increase, capacitor fast charging in current follow-up circuit 33, in the time that voltage declines from peak value, electric capacity discharges rapidly, give load afterflow, next stage, power supply can be given again capacitor charging, go round and begin again and form pulsating dc voltage at load two ends, it is continuous that source current waveform progressively tends to, diode in circuit also can effectively reduce the peak current in reciprocal charging process, by add high-frequency filter capacitor between by stream power factor correction stage and rear class resonant transformation, output voltage waveforms is improved greatly, THD value obviously reduces.
The embodiment of the present invention is by splitting into a diode between electric capacity in traditional current follow-up circuit two diode series connection, and at two diodes and the middle high-frequency filter capacitor that adds of rear class resonant transformation drive circuit, can effectively improve output voltage waveforms, obviously reduce the THD value causing due to input current spike, and can effectively improve the power factor of electric ballast, harmonic reduction current interference.
The current follow-up circuit that the embodiment of the present invention provides is applied to after electric ballast, can improve the waveform of power supply input current, reduce the harmonic content in input current, and while reducing to use electric ballast in enormous quantities to the neutral line current in three-phase power line, thereby can greatly reduce the pollution to electrical network, improve the security performance of three phase supply.In addition, can also improve line power factor, reduce the loss of supply line, direct current average output voltage Vo is reduced, transistorized functional reliability improves, thereby the functional reliability of electric ballast also can be improved.Secondly, also reduce surge starting current, increased the functional reliability of three-phase power supply system.In addition, can reduce the capacity of capacitor C 8, C9 and withstand voltage, improve its functional reliability.Because the capacity of electrochemical capacitor C8, C9 can reduce, thus can replace electrochemical capacitor with polypropylene capactive, thus solve the poor problem of functional reliability under electrochemical capacitor high temperature, high pressure.
The foregoing is only preferred embodiment of the present invention, not in order to limit the present invention, all any modifications of doing within the spirit and principles in the present invention, be equal to and replace and improvement etc., within all should being included in protection scope of the present invention.
Claims (9)
1. an electronic ballast starting circuit, is characterized in that, described start-up circuit comprises:
High-frequency filter circuit, incoming transport electricity, for carrying out High frequency filter to exchanging input, eliminates High-frequency Interference;
Bridge rectifier, is connected with described high-frequency filter circuit, for the alternating current after described high-frequency filter circuit High frequency filter being carried out to rectification, output ripple direct current;
Current follow-up circuit, is connected with described bridge rectifier, proofreaies and correct for the power factor to described pulsating direct current, suppresses input current spike composition; And
Resonant transformation drive circuit, is connected with described current follow-up circuit, for further eliminating the humorous wave interference of described pulsating direct current, drives rear class load;
Described current follow-up circuit comprises:
Diode D8, D7, D6 and the D5 of series connection successively, the anode of described diode D8 connects described resonant transformation drive circuit, and the negative electrode of described diode D5 connects the common cathode limit of described bridge rectifier;
Capacitor C 8, its one end connects the contact in the middle of described diode D7, D8, and the other end connects described resonant transformation drive circuit;
Capacitor C 9, its one end connects the common anode limit of described bridge rectifier, and the other end connects the contact in the middle of described diode D5, D6; And
High-frequency filter capacitor, one end connects the contact of described diode D6, D7, and the other end connects described resonant transformation drive circuit;
In the time that input voltage changes from zero toward peak value Vm with sinusoidal rule, the series loop charging that capacitor C 8, diode D7, D6 and capacitor C 9 form provides electric current to load simultaneously.
2. electronic ballast starting circuit as claimed in claim 1, is characterized in that, described high-frequency filter capacitor comprises:
Capacitor C 10 and capacitor C 11;
One end of described capacitor C 10 connects the contact of described diode D6, D7, and the other end connects one end of described resonant transformation drive circuit;
One end of described capacitor C 11 connects the contact of described diode D6, D7, and the other end connects the other end of described resonant transformation drive circuit.
3. electronic ballast starting circuit as claimed in claim 1, is characterized in that, described capacitor C 8 and capacitor C 9 are electrochemical capacitor.
4. electronic ballast starting circuit as claimed in claim 1, is characterized in that, described capacitor C 8 and capacitor C 9 are polypropylene capactive.
5. an electric ballast, comprises start-up circuit, it is characterized in that, described start-up circuit comprises:
High-frequency filter circuit, incoming transport electricity, for carrying out High frequency filter to exchanging input, eliminates High-frequency Interference;
Bridge rectifier, is connected with described high-frequency filter circuit, for the alternating current after described high-frequency filter circuit High frequency filter being carried out to rectification, output ripple direct current;
Current follow-up circuit, is connected with described bridge rectifier, proofreaies and correct for the power factor to described pulsating direct current, suppresses input current spike composition; And
Resonant transformation drive circuit, is connected with described current follow-up circuit, for further eliminating the humorous wave interference of described pulsating direct current, drives rear class load;
Described current follow-up circuit comprises:
Diode D8, D7, D6 and the D5 of series connection successively, the anode of described diode D8 connects described resonant transformation drive circuit, and the negative electrode of described diode D5 connects the common cathode limit of described bridge rectifier;
Capacitor C 8, its one end connects the contact in the middle of described diode D7, D8, and the other end connects described resonant transformation drive circuit;
Capacitor C 9, its one end connects the common anode limit of described bridge rectifier, and the other end connects the contact in the middle of described diode D5, D6; And
High-frequency filter capacitor, one end connects the contact of described diode D6, D7, and the other end connects described resonant transformation drive circuit;
In the time that input voltage changes from zero toward peak value Vm with sinusoidal rule, the series loop charging that capacitor C 8, diode D7, D6 and capacitor C 9 form provides electric current to load simultaneously.
6. electric ballast as claimed in claim 5, is characterized in that, described high-frequency filter capacitor comprises:
Capacitor C 10 and capacitor C 11;
One end of described capacitor C 10 connects the contact of described diode D6, D7, and the other end connects one end of described resonant transformation drive circuit;
One end of described capacitor C 11 connects the contact of described diode D6, D7, and the other end connects the other end of described resonant transformation drive circuit.
7. electric ballast as claimed in claim 5, is characterized in that, described capacitor C 8 and capacitor C 9 are electrochemical capacitor.
8. electric ballast as claimed in claim 5, is characterized in that, described capacitor C 8 and capacitor C 9 are polypropylene capactive.
9. the lighting apparatus of an electric ballast that comprises the arbitrary claim of claim 5 to 8.
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| CN201010191174.2A CN101883464B (en) | 2010-06-02 | 2010-06-02 | Current follow-up passive factor correction circuit and electronic ballast starting circuit |
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| CN201010191174.2A CN101883464B (en) | 2010-06-02 | 2010-06-02 | Current follow-up passive factor correction circuit and electronic ballast starting circuit |
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| CN101883464A CN101883464A (en) | 2010-11-10 |
| CN101883464B true CN101883464B (en) | 2014-06-25 |
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Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN102394556A (en) * | 2011-11-16 | 2012-03-28 | 上海能巍电气科技有限公司 | Charge power factor correction circuit |
| CN103023350B (en) * | 2012-11-02 | 2015-07-15 | 东莞市神牛电子科技有限公司 | Asymmetric capacitor energy storage type AC (Alternating Current)-DC (Direct Current) power source |
| CN109039110A (en) * | 2018-07-11 | 2018-12-18 | 佛山市众盈电子有限公司 | A kind of commercial power rectification circuit |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1753594A (en) * | 2005-10-27 | 2006-03-29 | 横店得邦电子有限公司 | Electron ballast passive power factor correcting circuit |
| CN2879589Y (en) * | 2006-02-14 | 2007-03-14 | 马守本 | Electronic blast |
| CN201611975U (en) * | 2010-01-28 | 2010-10-20 | 广东锦力电器有限公司 | Electronic ballast for high-power energy-saving lamp |
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Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1753594A (en) * | 2005-10-27 | 2006-03-29 | 横店得邦电子有限公司 | Electron ballast passive power factor correcting circuit |
| CN2879589Y (en) * | 2006-02-14 | 2007-03-14 | 马守本 | Electronic blast |
| CN201611975U (en) * | 2010-01-28 | 2010-10-20 | 广东锦力电器有限公司 | Electronic ballast for high-power energy-saving lamp |
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