CN101873755B - Discharge lamp lighting device and illuminator - Google Patents

Abstract

The invention provides a discharge lamp lighting device, a power supply device and an illuminator, which can prevent an overlarge electric stress on a circuit element or the discharge clamp after lighting the lamp. The device is provided with a direct current power supply part, a resonance part formed a resonance circuit together with the discharge lamp. A switch part for switching the DC power supply part and the resonance part, and a driving part for driving the switch part to output an alternated current to the discharge lamp from the resonance part through the voltage frequencies on two ends of a controlling capacitor. After the driving part is started and still cannot work in a preset stopping time T1, the driving part starts to work after stopping for the stopping time T1. The voltages on two ends of the capacitor can be stabled in the stopping time T1, so the overlarge electric stress on the circuit element or the discharge clamp can be avoided after starting, even if starting again after stopping for a short period of time.

Description

Discharge lamp ignition device and ligthing paraphernalia

Technical field

The present invention relates to discharge lamp ignition device, supply unit and ligthing paraphernalia.

background technology

In the past, a kind of discharge lamp ignition device is provided, possess output direct current power DC power supply portion, form together with discharge lamp the resonant structure of resonant circuit, at least comprise 1 switch element and along with the conducting of this switch element disconnect and switch DC power supply portion and the switch portion being connected of resonant structure and by the switch element conducting of switch portion is disconnected drive and from resonant structure the drive division (for example, with reference to patent documentation 1 and patent documentation 2) to discharge lamp supply alternating electromotive force.The resonance frequency of the resonant circuit that can form by discharge lamp and resonant structure to the output power of discharge lamp, with drive division, the relation of the frequency (hereinafter referred to as " operating frequency ") of the action of switch portion ON/OFF is controlled.

In this discharge lamp ignition device, what have possesses control capacitor, and drive division is configured to the operating frequency action corresponding to controlling by the both end voltage of capacitor.In this discharge lamp ignition device, by being controlled with capacitor charging/discharging by the circuit of controlling use, change the operating frequency of drive division, can control thus the output power to discharge lamp.In addition, when the change of operating frequency, by control, use the time constant of capacitor, operating frequency and gradually changing to the output power of discharge lamp, thus with make operating frequency and compared with the situation of stepped variation, on circuit element and discharge lamp, be difficult for effect electric stress to the output power of discharge lamp.

But, in above-mentioned discharge lamp ignition device, controlling after the stopping of short time and restarting while there is no abundant recovery by the both end voltage of capacitor because electric discharge waits, after just starting, the output power of resonant structure temporarily exceedingly becomes large, likely on circuit element and discharge lamp, acts on excessive electric stress.

In addition, in the past known by the direct voltage from DC power supply or be wish big or small direct voltage and this direct voltage is transformed to high frequency voltage again and the load of discharge lamp etc. is supplied with to the supply unit of action electric power from the AC voltage conversion of AC power.As the mapping device of the direct voltage to hope size in such supply unit, use widely and can guarantee stable output voltage and can improve the DC power supply circuit being formed by boost chopper electric current of the distortion of input current waveform large-scale input supply voltage.

The elemental motion of DC power supply circuit is generally for example in patent documentation 3, to disclose such action, by the switch motion of switch element, repeatedly carry out to the savings of the energy of inductor and from the release of the savings energy of inductor, this is released energy and is supplied with to the load circuit that comprises discharge lamp via diode and smoothing capacitor.Inductor is connected in the mode of putting aside energy when the conducting of switch element, detects the switching current that flows through this switch element, if this current value reaches setting, controls, so that switch element is switched to disconnection.Above-mentioned switch element is switched to the setting of disconnection, by output voltage this detection voltage of use error amplifier FEEDBACK CONTROL of detecting boost chopper, decide.In addition the timing that, switch element is switched to conducting decides by the timing that is detected inductor release savings energy by zero current detection portion.

In zero current detection portion, secondary coiling is set in inductor, by monitor that the voltage producing detects the timing of inductor release savings energy in this secondary coiling.; because the voltage producing in secondary coiling is when the energy savings of inductor and the polarity inversion of while release; if so for example connecting secondary winds the line so that it produces negative voltage when energy is put aside; when energy discharges, be reversed to immediately positive voltage, after energy discharges, converge near the voltage about 0V.So near the voltage 0V in the moment declining from positive voltage by supervision, can detect the exergonic timing of savings of inductor.

In addition, the output voltage of the input power of DC power supply circuit is for example 100V～200V, at the output voltage of input power, be in high-tension situation, control as the afore mentioned rules value of the electric current that flows through switch element when disconnecting diverter switch element from conducting is lower so that compared with the situation that the situation that output voltage is 200V is 100V with output voltage the conduction period of switch element shorter.

On the other hand, forming in the diode of DC power supply circuit, when when changing reverse blas into along bias voltage, because the impact of the charge carrier put aside when along bias voltage has the contrary recovery time of short time to contrary direction current flowing.Thereby, when switch element switches to conducting from disconnecting, during the contrary recovery time of this diode, likely from smoothing capacitor to switch element, supply with larger electric current.

In boost chopper in the past, in the case of the output voltage of input power temporary low, even if switch element switches to conducting, can not in inductor, put aside sufficient energy.But, owing to as described above the afore mentioned rules value of the electric current that flows through switch element being set lowlyer, so owing to being the switching current that flows through switch element by the electric current error detection flowing through, therefore switch element is switched to disconnection under the inadequate state of savings of the energy to inductor in the contrary recovery time of above-mentioned diode.So the energy of savings in inductor is insufficient, so the energy of savings is by abrupt release, detect that the zero current detection portion of this situation switches to conducting by switch element.Therefore, if the abnormal continuation of input power, switch element sometimes with the very short cycle, particularly with nanosecond unit's ON/OFF repeatedly, likely because switching losses increases switch element heat damage.

In addition, provided in the past and possessed the supply unit (for example, with reference to patent documentation 4) of being exported the DC power supply portion of direct current power and the power converter portion by the direct current power proper transformation of DC power supply portion output and to load output by the power supply supply electric power from outside.Load is for example discharge lamp, and power converter portion is for example converter circuit.

And then, in this supply unit, the abnormal judging part of the mains side having or not that possesses the abnormality that judges DC power supply portion having and the abnormal judging part of the load-side having or not that judges at least one party's of power converter portion and load abnormality.As the abnormality by the abnormal judging part judgement of mains side, for example there is the low state of the output voltage of DC power supply portion, as the abnormality by the abnormal judging part judgement of load-side, for example, there is load not correctly to be connected to the no-load condition in power converter portion.

The abnormal judgement that the abnormal judging part of mains side carries out, for example situation about eliminating at short notice because of the temporary grade lowly causing of the input electric power to DC power supply portion mostly, so as the action being judged as by the abnormal judging part of mains side when abnormal, not to make immediately the output of power converter portion stop, and be preferably made as, temporarily make the output power of power converter portion reduce such action.

But, because power converter portion is located at the rear class of DC power supply portion, so when being judged as abnormality by the abnormal judging part of mains side, the situation that erroneous judgement is abnormality in the abnormal judging part of load-side is more.And, if be configured to, when being judged as abnormality by the abnormal judging part of load-side, make DC power supply portion and power converter portion stop action,, due to because erroneous judgement as described above stops, likely not making in fact the output power of power converter portion reduce such action.

[patent documentation 1] TOHKEMY 2004-327116 communique

[patent documentation 2] TOHKEMY 2008-269860 communique

[patent documentation 3] TOHKEMY 2003-217883 communique

[patent documentation 4] TOHKEMY 2005-19172 communique

Summary of the invention

The present invention makes in view of above-mentioned reason, its objective is a kind of discharge lamp ignition device and the ligthing paraphernalia that can avoid acting on excessive electric stress after just starting on circuit element or discharge lamp is provided.

Another object of the present invention be to provide a kind of can prevent from having occurred in the output voltage of input power abnormal the supply unit that damages of switch element.

Another object of the present invention is to provide the supply unit stopping that a kind of erroneous judgement that can suppress abnormality causes.

According to the 1st mode of the present invention, it is characterized in that possessing: DC power supply portion, output direct current power; Resonant structure forms resonant circuit together with discharge lamp; Switch portion, at least comprises 1 switch element, along with the conducting of this switch element disconnects and switches being connected of DC power supply portion and resonant structure; Drive division, disconnects the switch element of driving switch portion by conducting, from resonant structure, discharge lamp is supplied with to alternating electromotive force; Control part, by controlling the frequency of action of drive division, controls the frequency of the alternating electromotive force to discharge lamp output from resonant structure; Driving power portion is supplied with electric power from switch portion after the action of drive division starts, output direct current power; Startup portion is supplied with electric power from DC power supply portion before the action of drive division starts, and driving power portion is supplied with to electric power; Control power supply unit, from driving power portion, supplied with electric power, the output voltage of driving power portion be more than the reference voltage of regulation during in, generate the direct current power as the power supply of control part, control part is supplied with; Operating frequency as the frequency of drive division driving switch portion determines according to the both end voltage of the control capacitor that makes both end voltage change corresponding to the output of control part; Control part is when the startup of discharge lamp, after by each filament of discharge lamp, the preheating of preheating is moved respectively, start the startup of the lighting a lamp action of discharge lamp, then make the both end voltage of controlling with capacitor change, to transfer to the operating stably of lighting a lamp of sustain discharge lamp; Drive division from after controlling the output of electric power of power supply unit, does not make action start in beginning in the dwell time of regulation.

According to the 1st mode of the present invention, owing to can make the both end voltage of controlling with capacitor in dwell time, stablize, even so the situation of restarting after the stopping of short time also can avoid that the output power of resonant structure after just starting is provisional exceedingly to be become large and forming on the circuit element of resonant structure or discharge lamp and act on excessive electric stress.

According to the 2nd mode of the present invention, it is characterized in that, possess: DC power supply circuit, there is at least 1 inductor and be connected in series in the switch element on inductor, by the ON/OFF of diverter switch element, repeatedly carry out to the savings of the energy of inductor and from the release of the energy of inductor, by being transformed to direct voltage from the direct voltage of DC power supply or from the pulsating voltage after the ac voltage rectifier of AC power; Load circuit, accepts the output voltage of DC power supply circuit, and load is supplied with to action electric power; Output voltage test section, the output voltage of detection DC power supply circuit; DC power control circuit, by according to the testing result of output voltage test section, switch DC power supply circuit switch element ON/OFF and by the output voltage control of DC power supply circuit, be the big or small voltage of regulation; DC power control circuit has: zero current detection portion, if flow through current value that the electric current of inductor becomes regulation with next output zero-signal; Peak current detection portion, if flow through current value that the electric current of the switch element of DC power supply circuit becomes regulation above, exports peak signal; Drive division, switches to the switch element of DC power supply circuit conducting and according to peak signal, the switch element of DC power supply circuit is switched to disconnection according to zero-signal; Zero current detection portion possesses to be become the current value of the regulation zero-signal after following by the electric current that flows through inductor and exports to the shielding part that the action of drive division stops specified time limit.

According to the 2nd mode of the present invention, provisional low and can not put aside sufficient energy in inductor in the situation that, can prevent that the switch element moment of DC power supply circuit from switching to conducting at the output voltage of input power.Thereby, even in the case of the output voltage of input power occurred abnormal, the switch element that also can prevent DC power supply circuit occurs with the situation of very short cycle switched conductive/disconnection, can prevent the cause thermal damage of the switch element that the increase of switching losses causes.

According to the 3rd mode of the present invention, it is characterized in that possessing: DC power supply portion, is supplied with electric power by the power supply from outside, output direct current power; Power converter portion, exports the direct current power proper transformation of DC power supply portion output to load; The abnormal judging part of mains side, judges the having or not of abnormality of DC power supply portion; The abnormal judging part of load-side, judges at least one the having or not of abnormality of power converter portion and load; Control part, at least controls power converter portion according to the judgement of the judgement of the abnormal judging part of mains side and the abnormal judging part of load-side; Control part when starting, start before operating stably, make output power from from power converter portion to load than startup action few operating stably; Control part, when being judged as abnormality by the abnormal judging part of mains side, carries out startup action again lasting specified time limit; When being judged as abnormality by the abnormal judging part of load-side, only, in the situation that not being judged as abnormality by the abnormal judging part of mains side, at least make the output of power converter portion stop.

According to the 3rd mode of the present invention, make action that the judgement of the abnormality of carrying out based on the abnormal judging part of mains side starts startup action again make action that power converter portion stops more preferably than the judgement of the abnormality of carrying out based on the abnormal judging part of load-side, thus be difficult for occurring along with DC power supply portion extremely and the stopping of the power converter portion being caused for abnormality by the abnormal judging part erroneous judgement of load-side.

Accompanying drawing explanation

Fig. 1 is the key diagram that represents an example of the action of embodiments of the present invention 1, Fig. 1 (a) represents that the time of controlling voltage changes, Fig. 1 (b) represents to change to the time of the input voltage that stops enforcement division, Fig. 1 (c) represents that the time of the output voltage that stops enforcement division changing, the time of the output voltage of Fig. 1 (d) order of representation control part changes, Fig. 1 (e) represents to control the time variation by the both end voltage of capacitor, and Fig. 1 (f) represents that the time of operating frequency changes.

Fig. 2 is the circuit module figure that represents execution mode 1.

Fig. 3 is the circuit module figure that represents the startup portion of execution mode 1 and control power supply unit.

Fig. 4 is the key diagram that represents an example of the action of execution mode 1, Fig. 4 (a) represents that the time of the output voltage of DC power supply portion changes, Fig. 4 (b) represents respectively the time of the each detection voltage after driving voltage dividing potential drop and driving voltage to change, Fig. 4 (c) represents that the time of the grid voltage of the 1st switch element of startup portion changes, Fig. 4 (d) represents that the time of controlling voltage changes, Fig. 4 (e) represents that the time of the output voltage that stops enforcement division changing, Fig. 4 (f) represents that the time of the magnitude of voltage of the driving signal to switch portion a switch element output from drive division changes.

Fig. 5 is oscillating portion, the drive division that represents execution mode 1 and the circuit module figure that stops enforcement division.

Fig. 6 is the key diagram that represents the action of the oscillating portion of execution mode 1, Fig. 6 (a) represents that the time of the both end voltage of the vibration capacitor of oscillating portion changes, Fig. 6 (b) represents that the time of the output voltage of the comparator of oscillating portion changes, Fig. 6 (c) represents the time variation of the magnitude of voltage of the 1st rectangular signal, and Fig. 6 (d) represents that the 1st drives the time of the magnitude of voltage of signal to change.

Fig. 7 is the circuit module figure that represents embodiments of the present invention 2.

Fig. 8 is the circuit module figure that represents embodiments of the present invention 3.

Fig. 9 is the circuit module figure that represents the major part of execution mode 3.

Figure 10 is the key diagram that represents an example of the action of execution mode 3, Figure 10 (a) represents that the time of controlling voltage changes, Figure 10 (b) represents that the time of the output voltage that regulates control part changes, the time of the output voltage of Figure 10 (c) order of representation control part changes, Figure 10 (d) represents to control the time variation by the both end voltage of capacitor, and Figure 10 (f) represents that the time of operating frequency changes.

Figure 11 is the circuit module figure that represents the major part of the comparative example of execution mode 3.

Figure 12 represents the example that the time of the input voltage of the operational amplifier of the input to oscillating portion of execution mode 3 changes, and Figure 12 (a) represents that environment temperature is near situation normal temperature, and Figure 12 (b) represents that environment temperature is the situation of low temperature.

Figure 13 is illustrated in execution mode 3 to the input input voltage of non-reversion input terminal of operational amplifier and the key diagram of the relation of lamp electric power.

Figure 14 is the key diagram that is illustrated in the relation of environment temperature and lamp current and lamp electric power in execution mode 3.

Figure 15 is the circuit module figure that represents embodiments of the present invention 4.

Figure 16 is the key diagram that represents an example of the action of execution mode 4, Figure 16 (a) represents that the time of controlling voltage changes, Figure 16 (b) represents from stopping the time variation of enforcement division to the output voltage of drive division, Figure 16 (c) represents that the time of report voltage changes, Figure 16 (d) represents the time variation of the magnitude of voltage of the driving signal to switch portion a switch element output from drive division, and Figure 16 (e) represents that the time of clock frequency changes.

Figure 17 is the circuit module figure that represents embodiments of the present invention 5.

Figure 18 is the light a lamp key diagram of time and an example of the relation of light modulation ratio of the accumulative total that represents execution mode 5.

Figure 19 is the circuit module figure that represents embodiments of the present invention 6.

Figure 20 is the circuit module figure that represents the power supply test section of execution mode 6 and stop enforcement division.

Figure 21 is the key diagram that represents an example of the action of execution mode 6, Figure 21 (a) represents that the time of the output voltage of stop control unit changes, Figure 21 (b) represents that the time of the output voltage of power supply test section changes, Figure 21 (c) is illustrated in the time variation that stops the output voltage that is connected to the input comparator on power supply test section in enforcement division, Figure 21 (d) represents that the time that stops the logic of enforcement division and the output voltage of circuit changes, Figure 21 (e) represents to postpone the time variation by the both end voltage of capacitor, Figure 21 (f) represents that the time of report voltage changes.

Figure 22 is the circuit module figure that represents the power supply test section of execution mode 6 and stop the modification of enforcement division.

Figure 23 is the circuit module figure that represents embodiments of the present invention 7.

Figure 24 is the circuit module figure that represents embodiments of the present invention 8.

Figure 25 is the circuit module figure that represents the major part of execution mode 8.

Figure 26 is the circuit module figure that represents embodiments of the present invention 9.

Figure 27 is the circuit diagram that represents the low test section of direct voltage of execution mode 9.

Figure 28 is the key diagram that does not reach duration of being illustrated in the low state of direct voltage in execution mode 9 action in the situation of the time of restarting, Figure 28 (a) represents that the time of the output voltage of DC power supply test section changes, Figure 28 (b) represents that the time of the output voltage of the comparator of the low judging part of direct voltage changes, Figure 28 (c) represents that the time of the output voltage of the low judging part of direct voltage changes, the time of the output voltage of Figure 28 (d) order of representation control part changes, Figure 28 (e) represents that the time of operating frequency changes, Figure 28 (f) represents that stop control unit is to the time variation driving with the output voltage of integrated circuit.

Figure 29 is the key diagram that does not reach duration of being illustrated in the low state of direct voltage in execution mode 9 action in the situation of the time of restarting, Figure 29 (a) represents that the time of the output voltage of DC power supply test section changes, Figure 29 (b) represents that the time of the output voltage of the comparator of the low judging part of direct voltage changes, Figure 29 (c) represents that the time of the output voltage of the low judging part of direct voltage changes, the time of the output voltage of Figure 29 (d) order of representation control part changes, Figure 29 (e) represents that the time of operating frequency changes, Figure 29 (f) represents that stop control unit is to the time variation driving with the output voltage of integrated circuit.

Figure 30 is the circuit module figure that represents the major part of embodiments of the present invention 10.

Figure 31 is the key diagram that represents the action of the zero current detection portion of execution mode 10, Figure 31 (a) represents that the time of the output voltage of power drives portion changes, Figure 31 (b) represents to change to the time of the input voltage of zero current detection portion, Figure 31 (c) changes the time that represents the output voltage of the input comparator of zero current detection portion, Figure 31 (d) represents that the time of the both end voltage of the reservation capacitor of zero current detection portion changes, Figure 31 (e) represents that the time of the output voltage of single-shot trigger circuit changes, Figure 31 (f) represents that the time of the output voltage of the output comparator of zero current detection portion changes, Figure 31 (g) represents that the time of the output voltage of zero current detection portion changes.

Figure 32 is the circuit module figure that represents execution mode 10.

Figure 33 is the circuit module figure that represents the major part of embodiments of the present invention 11.

Figure 34 is the key diagram that represents the action of execution mode 11, Figure 34 (a) represents that the time of the output voltage of report portion changes, Figure 34 (b) represents the time variation of the output voltage from resonant structure to discharge lamp, and Figure 34 (c) represents that the time of operating frequency changes.

Figure 35 is the circuit module figure that represents embodiments of the present invention 12.

Figure 36 is the circuit module figure that represents the major part of execution mode 12.

Figure 37 is the circuit module figure that represents the major part of the modification of execution mode 12.

Figure 38 is the key diagram that represents the example of the configuration on the printed wiring board of the circuit element that forms execution mode 12.

Figure 39 is the key diagram that represents the comparative example of execution mode 12.

Figure 40 (a)～Figure 40 (c) represents respectively execution mode 12 to be accommodated in the state in housing, and Figure 40 (a) is vertical view, and Figure 40 (b) is front view, and Figure 40 (c) is right side view.

Figure 41 is the stereogram that represents the example of the ligthing paraphernalia that uses execution mode 12.

Figure 42 is another the routine stereogram that represents the ligthing paraphernalia that uses execution mode 12.

Figure 43 is the circuit diagram representing about the execution mode 13 of supply unit of the present invention.

Figure 44 is the startup portion that represents execution mode 13, the circuit diagram of controlling power supply comparing section and the 1st control power supply generating unit.

Figure 45 (a)～Figure 45 (g) is the time diagram of the action of the control circuit for execution mode 13 is described.

Figure 46 is the circuit diagram that represents the converter control circuit of execution mode 13.

Figure 47 (a)～Figure 47 (g) is the time diagram of the sequential control for execution mode 13 is described.

Figure 48 is the circuit diagram that stops enforcement division that represents execution mode 13.

Figure 49 is the flow chart of the elemental motion of the action initialization circuit for execution mode 13 is described.

Figure 50 is the circuit diagram that represents the zero current detection portion of execution mode 13.

Figure 51 (a)～Figure 51 (f) is the time diagram of the action of the zero current detection portion for execution mode 13 is described.

Figure 52 is the circuit diagram representing about the zero current detection portion of the execution mode 14 of supply unit of the present invention.

Figure 53 is the circuit diagram that represents the filter portion of execution mode 14.

Figure 54 (a)～Figure 54 (e) is the time diagram of the action of the zero current detection portion for execution mode 14 is described.

Figure 55 is the circuit diagram representing about the execution mode 15 of supply unit of the present invention.

Figure 56 is the circuit diagram that represents the low judging part of voltage of execution mode 15.

Figure 57 (a)～Figure 57 (f) is the time diagram of the action of the low judging part of voltage in the temporary low situation of the output voltage for execution mode 15 is described.

Figure 58 (a)～Figure 58 (f) is the time diagram of the action of the low judging part of voltage in the situation that the output voltage continuation for execution mode 15 is described is low.

Figure 59 is the flow chart of the abnormal judgement processing for execution mode 15 is described.

Figure 60 is the circuit diagram representing about the execution mode 16 of supply unit of the present invention.

Figure 61 is the circuit diagram that represents the voltage rising judging part of execution mode 16.

Figure 62 (a)～Figure 62 (d) is voltage rising judging part for execution mode 16 is described and the time diagram of the action of start portion again.

Figure 63 is the circuit module figure that represents embodiments of the present invention 17.

Figure 64 is the key diagram that represents an example of the action of execution mode 17, Figure 64 (a) represents that the time of controlling voltage changes, Figure 64 (b) represents to change to the time of the input voltage that stops enforcement division, Figure 64 (c) represents that the time of the output voltage that stops enforcement division changing, the time of the output voltage of Figure 64 (d) order of representation control part changes, Figure 64 (e) represents to control the time variation by the both end voltage of capacitor, Figure 64 (f) represents the time variation of operating frequency, and Figure 64 (g) represents that the time of clock frequency changes.

Figure 65 is the circuit module figure that represents the major part of the modification of execution mode 17.

Figure 66 is the module map that represents embodiments of the present invention 18.

Figure 67 is the key diagram that represents an example of the action of execution mode 18, Figure 67 (a) represents that the time of controlling voltage changes, Figure 67 (b) represents that the time of the output voltage of stop control unit changes, Figure 67 (c) represents that the time of the output voltage that stops enforcement division changing, the time of the output voltage of Figure 67 (d) order of representation control part changes, Figure 67 (e) represents to control the time variation by the both end voltage of capacitor, and Figure 67 (f) represents that the time of operating frequency changes.

Figure 68 is the circuit module figure that represents embodiments of the present invention 19.

Embodiment

Below, with reference to accompanying drawing, to being used for implementing, of the present inventionly preferred embodiment describe.

(execution mode 1)

Present embodiment as shown in Figure 2, it is the device that the discharge lamp La of the general hot cathode type with a pair of filament (not shown) is lit a lamp, possess: rectification part DB, consists of known diode bridge, by the alternating electromotive force full-wave rectification of the AC power AC input from outside; DC power supply portion 1, by least smoothing and export direct current power of the output of rectification part DB; Switch portion 21, possesses the series circuit of two switch element Q10, Q20 between the output that is connected to DC power supply portion 1, using the two ends of the switch element Q20 of low voltage side (downside) as output; And resonant structure 22, be connected between the output of switch portion 21, form resonant circuit together with discharge lamp La.That is, switch portion 21 and resonant structure 22 form the converter circuit of so-called semi-bridge type as a whole.In addition the output head grounding of the low voltage side of DC power supply portion 1.

DC power supply portion 1 for example can consist of the smmothing capacitor (not shown) being connected between the output of rectification part DB, and in the case, the two ends of smmothing capacitor become the output of DC power supply portion 1.

In addition, resonant structure 22 possesses on the tie point of switch element Q10, Q20 that one end is connected to switch portion 21 and the other end is connected to the capacitor C2 on discharge lamp La via the capacitor C1 of discharge lamp La ground connection and the series circuit of inductor L1 and (between the filament of discharge lamp La) in parallel.

And then, present embodiment possess for when the startup of discharge lamp La by each filament of discharge lamp La preheating part 23 of preheating respectively.Preheating part 23 possess have on one end is connected to switch portion 21 tie point of switch element Q10, Q20 via capacitor C3 and the once coiling of other end ground connection and separately and the series circuit of capacitor C4, C5 be connected to the transformer Tr1 of two secondaries coilings between the two ends of each filament of discharge lamp La.

In addition, present embodiment possesses: drive division 31, via resistance R 1, R2, be connected to each switch element Q10, the Q20 of switch portion 21 respectively upper, by conducting, disconnect each switch element Q10, the Q20 of driving switch portion 21 and from resonant structure 22, discharge lamp La is supplied with to alternating electromotive force; And sequential control portion 41, by controlling the frequency of action of drive division 31, control the frequency of the alternating electromotive force to discharge lamp La output from resonant structure 22.

Drive division 31 is located at the driving consisting of high-withstand-voltage integrated circuit (HVIC) with in integrated circuit 3, and sequential control portion 41 is located at the control consisting of the integrated circuit that is called microcontroller (microcomputer) with in integrated circuit 4.As controlling with integrated circuit 4, if use the magnitude of voltage of input and output, be only 2 grades and do not comprise the structure of A/D converter and D/A converter, can suppress littlely with the power consumption in integrated circuit 4 by controlling.

In addition, present embodiment possesses the driving power portion 5 of the direct current power of the power supply of being supplied with electric power, output conduct driving integrated circuit 3 after the action of drive division 31 starts from switch portion 21.Driving power portion 5 possesses plus earth, and and negative electrode is connected to input side diode on the tie point of switch element Q10, Q20 of switch portion 21 and anodic bonding on the connecting portion of this input side diode and input side capacitor via input side capacitor, negative electrode is via the outlet side diode of the parallel circuits ground connection of outlet side capacitor C101 and Zener diode ZD1, and the both end voltage that makes outlet side capacitor C101 is output voltage.From the action of drive division 31 starts through the sufficient time and the stable state of the both end voltage of outlet side capacitor C101, the both end voltage of outlet side capacitor C101 is that the output voltage of driving power portion 5 for example becomes 10V.

And then, driving with in integrated circuit 3, be respectively equipped with before the action of drive division 31 starts, from DC power supply portion 1, supplied with electric power and export as the startup portion 32 of the direct current power of the power supply of driving power portion 5 and from driving power portion 5, supplied with electric power and the output voltage of driving power portion 5 be more than the reference voltage of regulation during generate as for example controlling, with the control voltage vcc 1 (5V) of the regulation of the power supply of integrated circuit 4 the control power supply unit 33 that control is supplied with integrated circuit 4.

If described in detail, as shown in Figure 3, the impedance component Z1 on the output that startup portion 32 has on the output of high-voltage side that one end is connected to DC power supply portion 1, the other end is connected to driving power portion 5 via the 1st switch element Q101.; in during the 1st switch element Q101 conducting of startup portion 32; the output voltage V dc of DC power supply portion 1 is outputed in driving power portion 5 via impedance component Z1 and the 1st switch element Q101, thus by the outlet side capacitor C101 charging of driving power portion 5.Above-mentioned the 1st switch element Q101 consists of the withstand voltage field-effect transistor of height of N-shaped raceway groove, the grid of the 1st switch element Q101 is connected on the tie point of DC power supply portion 1 and impedance component Z1 via resistance R 101, and via the series circuit of diode D101 and Zener diode ZD2 the parallel circuits ground connection with the 2nd switch element Q102 that formed by the field-effect transistor of N-shaped raceway groove.In addition, startup portion 32 has respectively by 4 divider resistances of the output voltage of driving power portion 5 (hereinafter referred to as " driving voltage ") Vcc2 dividing potential drop, from tie point different 3 kinds of detection voltage Va, Vb, the Vc of output voltage (voltage ratio) respectively of these divider resistances.And then startup portion 32 possesses in reversion and is transfused to the comparator C P1 on the 1st reference voltage Vr1 of regulation and lead-out terminal be connected to the 2nd switch element Q102 grid via logic and circuit OR1 in input terminal.In the non-reversion input terminal of comparator C P1, via the multiplexer TG1 that uses transmission gate circuit to form, be transfused to and detect voltage Vb, Vc.Above-mentioned multiplexer TG1 is connected on the lead-out terminal of comparator C P1, be configured to, in during the output H of comparator C P1 (height) level, the 2nd low detection voltage (hereinafter referred to as " the 2nd detects voltage ") Vb is input in the non-reversion input terminal of comparator C P1, minimum detection voltage (hereinafter referred to as " the 3rd detects voltage ") Vc is input in the non-reversion input terminal of comparator C P1 in during the output L of comparator C P1 (low) level.

Use Fig. 4 that the action of startup portion 32 is described.After power supply is just switched on, the output of comparator C P1 is L level, in the non-reversion of comparator C P1, inject terminal thus and input the 3rd and detect voltage Vc, and by the 2nd switch element Q102 is disconnected, by the Zener voltage of Zener diode ZD2 by the 1st switch element Q101 conducting.During the 1st switch element Q101 conducting, the outlet side capacitor C101 of driving power portion 5 is supplied to the output power of DC power supply portion 1 and is charged by the impedance component Z1 via startup portion 32 and the 1st switch element Q101, makes gradually both end voltage (driving voltage) Vcc2 increase.If the final the 3rd detects voltage Vc, reach the 1st reference voltage Vr1, the output of comparator C P1 becomes H level.So, to the input voltage of non-reversion input terminal, be changed to than the 3rd and detect the 2nd detection voltage Vb that voltage Vc is high, and by the 2nd switch element Q102 conducting is disconnected the 1st switch element Q101, stop the supply of the electric power from startup portion 32 to driving power portion 5.At this moment drive division 31, also do not start action, from switch portion 21, driving power portion 5 is not supplied with to electric power, so by the electric discharge of outlet side capacitor C101, driving voltage Vcc2 starts to decline.If the final the 2nd detects voltage Vb, reach the 1st reference voltage Vr1, the output of comparator C P1 becomes L level again, the output voltage of driving power portion 5 starts to rise, if then the 3rd detection voltage Vc reaches the 1st reference voltage Vr1, the output of comparator C P1 becomes H level again.Then, from DC power supply portion 1, supply with such direct current power shown in Fig. 4 (a), and shown in Fig. 4 (e) from stopping enforcement division 34 (aftermentioned) to the input L level of logic and circuit OR1 and drive division 31 stop during, by the repetition of above-mentioned action, the grid voltage of the 1st switch element Q101 changes as shown in Fig. 4 (c), it is the such upper voltage limit of the 1st reference voltage Vr1 that driving voltage Vcc2 detects voltage Vc the 3rd as shown in Fig. 4 (b), and the 2nd detect voltage Vb and repeatedly change up and down between the such lower voltage limit of the 1st reference voltage Vr1.

Here, driving with in integrated circuit 3, be provided with control respectively drive division 31 and startup portion 32 stop enforcement division 34.The output that stops enforcement division 34 is imported in logic and circuit OR1, in during stopping the output L level of enforcement division 34, drive division 31 is stopped and the electric power from startup portion 32 to driving power portion 5 is supplied with to conducting, in during stopping the output H level of enforcement division 34, by haveing nothing to do and disconnect by the 2nd switch element Q102 conducting, by the 1st switch element Q101 with the output of comparator C P1, the electric power from startup portion 32 to driving power portion 5 is supplied with and disconnected.Wherein, in during stopping the output H level of enforcement division 34, by drive division 31, move (generating the output of the driving use of switch element Q10, Q20 such shown in Fig. 4 (f)), the electric power carrying out from switch portion 21 to driving power portion 5 is supplied with.

In addition, control power supply unit 33 and possess the comparator C P2 that is transfused to detection voltage (hereinafter referred to as " the 1st detects voltage ") Va the highest in the detection voltage that the divider resistance of startup portion 32 exports and is transfused to the 1st reference voltage Vr1 in non-reversion input terminal in reversion input terminal, be connected to constant current circuit Ir1 between output and the earthing potential of driving power portion 5 and the series circuit of Zener diode ZD3, base stage is connected on the tie point of constant current circuit Ir1 and Zener diode ZD3 and collector electrode is connected on the output of driving power portion 5, emitter is connected to the transistor Q103 controlling by the npn type on integrated circuit 4 as the output of controlling power supply unit 33, and be connected in that the field-effect transistor by N-shaped raceway groove on Zener diode ZD3 forms in parallel and grid is connected to the switch element Q104 on the lead-out terminal of comparator C P2.; as shown in Fig. 4 (d); in being configured to only during the 1st detects voltage Va to exceed the 1st reference voltage Vr1, to controlling with integrated circuit 4, exporting and control voltage vccs 1; in during the 1st detection voltage Va is lower than the 1st reference voltage Vr1, does not export and control voltage vcc 1 (output voltage of controlling power supply unit 33 is roughly 0), driving voltage when the 1st detection voltage Va is the 1st reference voltage Vr1 is said reference voltage.Here, from driving the capacitor C51 ground connection of eliminating use via noise with the circuit that integrated circuit 3 uses integrated circuit 4 outputs to control voltage vcc 1 to control.

In addition, driving with in integrated circuit 3, be provided with the oscillating portion 35 of the output square wave corresponding with the frequency of the output of sequential control portion 41, drive division 31 disconnects switch element Q10, the Q20 of driving switch portion 21 with the frequency conducting of the output of oscillating portion 35.

Oscillating portion 35 as shown in Figure 5, possesses and by non-reversion input terminal, via resistance R 103, is connected in sequential control portion 41 and via resistance R 104 with control the parallel circuits ground connection of electricity consumption container C 103 and the input terminal that reverses is connected to that operational amplifier on lead-out terminal forms and lead-out terminal is transfused to the 2nd reference voltage Vr2 of regulation via the voltage follower OP1 of two resistance R 106, R102 ground connection and in non-reversion input terminal and the input terminal that reverses is connected to the control operational amplifier OP2 on the lead-out terminal of voltage follower OP1 via resistance R 106.The lead-out terminal of this operational amplifier OP2 is connected on the grid of charging switch element Qc, between this charging is connected in the charging current mirroring circuit CM1 that is transfused to respectively report voltage vcc 3 in each input output with switch element Qc and resistance R 102, above-mentioned charging with another output of current mirroring circuit CM1 via vibration electricity consumption container C 102 ground connection.In addition, oscillating portion 35 possesses the 1st electric discharge switch element Qd that being connected to via grid in input charging forms with the field-effect transistor by p-type raceway groove on an above-mentioned output of current mirroring circuit CM1 and is transfused to and reports voltage vcc 3 and on another input, connecting the electricity consumption container C 102 of vibrating, each output the electric discharge current mirroring circuit CM2 that distinguishes ground connection.And then oscillating portion 35 possesses reversion input terminal and is connected in vibration electricity consumption container C 102 and in non-reversion input terminal the comparator C P3 that is transfused to a side of the 4th reference voltage Vr4 of the 3rd reference voltage Vr3 of regulation and the low regulation of Bi 3 reference voltage Vr3 via the multiplexer TG2 that uses transmission gate circuit to form.On above-mentioned multiplexer TG2, connecting the lead-out terminal of comparator C P3, in during the output H level being configured at comparator C P3, the 3rd reference voltage Vr3 is input in the non-reversion input terminal of comparator C P3, the 4th reference voltage Vr4 is input in the non-reversion input terminal of comparator C P3 in during the output L of comparator C P3 level.In addition, in electric discharge, use on current mirroring circuit CM2, the 2nd electric discharge switch element Q105 that is being connected in parallel, the 2nd electric discharge consists of the field-effect transistor of N-shaped raceway groove with switch element Q105, and grid is connected on the lead-out terminal of comparator C P3.

Action to oscillating portion 35 describes.In vibration electricity consumption container C 102, do not have under fully charged state, comparator C P3 is output as H level, thus, is transfused to the 3rd reference voltage Vr3, by switch element Q105 conducting in the non-reversion input terminal of comparator C P3.During this period, by being connected in the conducting of the 2nd electric discharge switch element Q105 on electric discharge current mirroring circuit CM2 in parallel, suppressed with the electric discharge of the vibration electricity consumption container C 102 of current mirroring circuit CM2 via electric discharge, by the charging with current mirroring circuit CM1 via charging, the both end voltage of vibration electricity consumption container C 102 rises gradually.If finally vibrated, the both end voltage of electricity consumption container C 102 reaches the 3rd reference voltage Vr3, the output of comparator C P3 becomes L level, input voltage to the non-reversion input terminal of comparator C P3 becomes the 4th reference voltage Vr4, and the 2nd electric discharge is disconnected with switch element Q105.So, via electric discharge, with the discharging current of current mirroring circuit CM2, becoming than many via the charging current of charging current mirroring circuit CM1, the both end voltage of the electricity consumption container C 102 of vibrating thus declines gradually.And if the both end voltage of vibration electricity consumption container C 102 reaches the 4th reference voltage Vr4, the output of comparator C P3 becomes H level again, below repeats same action.Thus, the both end voltage of vibration electricity consumption container C 102 repeatedly changes up and down as shown in Fig. 6 (a) to the input voltage of the reversion input terminal of comparator C P3 between the 3rd reference voltage Vr3 and the 4th reference voltage Vr4, and the output of comparator C P3 becomes such square wave shown in Fig. 6 (b).And then oscillating portion 35 has the output Shaping circuit 35a that the output Shaping of comparator C P3 is exported to drive division 31.Output Shaping circuit 35a has the 1st rectangular signal generating unit (not shown) that generates the 1st rectangular signal as shown in Fig. 6 (c) by the output of comparator C P3 being carried out to for example two divided-frequency, generation is by the 2nd rectangular signal generating unit (not shown) of the 2nd rectangular signal of the output reversion of the 1st rectangular signal, and drive signal and drive signal to drive signal and the 2nd to drive signal to output to respectively generating unit dead time (not shown) drive division 31 by the 1st by making the timing of ON (conducting) of the 2nd rectangular signal generate the 2nd with above-mentioned same delay by making td dead time of constant time lag regulation of ON (conducting) (reversion from L level to H level) of the 1st rectangular signal generate shown in Fig. 6 (d) the such the 1st.The switch element Q10 that drive division 31 has switch portion of making 21 in the 1st drives conduction period (during H level) of signal conducting and the 1st drive the OFF (disconnections) of signal during (during L level) the 1st drive division 31a of breaking and another switch element Q20 of making switch portion 21 conducting and the 2nd drive division 31b that breaks during the OFF (disconnection) of the 2nd driving signal in the conduction period of the 2nd driving signal.That is,, by above-mentioned dead time of generating unit, prevent that two switch element Q10, Q20 of switch portion 21 are by while conducting.In said structure, for vibration electricity consumption container C 102, do not require extra high capability value, so vibration electricity consumption container C 102 can be in control with forming in integrated circuit 4.

Here, charging current and the discharging current of vibration electricity consumption container C 102 are respectively: higher less to controlling input voltage both end voltage higher, that control electricity consumption container C 103 with the reversion input terminal of operational amplifier OP2.That is, the above-mentioned the 1st drive signal and the 2nd drive the frequency of frequency, the i.e. action of drive division 31 of signal and the frequency of the alternating electromotive force to discharge lamp La output (hereinafter referred to as " and operating frequency) be: the both end voltage of controlling electricity consumption container C 103 is higher lower.

Control with the sequential control portion 41 of integrated circuit 4 by the time starting according to the supply from control voltage vcc 1 shown in Fig. 1 (a), the both end voltage of the control electricity consumption container C 103 shown in Fig. 1 (e) is changed, thus after by the preheating action t1～t2 of each filament difference preheating of discharge lamp La, make the startup action t2～t3 of the beginning of lighting a lamp of discharge lamp La, then transfer to the operating stably t3～t4 lighting a lamp of sustain discharge lamp La.For example, sequential control portion 41 is the unit to pwm signal such shown in control electricity consumption container C 103 output maps 1 (d) via resistance R 103, by the duty ratio of this pwm signal, the both end voltage of controlling electricity consumption container C 103 is changed.Particularly, by making said PWM signal stop (in other words making above-mentioned duty ratio is 0) in preheating action t1～t2, improve above-mentioned duty ratio than starting action t2～t3 in operating stably t3～t4, make thus to control electricity consumption container C 103 the both end voltage stage rise, as shown in Fig. 1 (f), make the interim decline of operating frequency f1～f3.That is, make operating frequency is the highest operating frequency f1 in t1～t2 is moved in preheating, starting in action t2～t3, is than the low operating frequency f2 of preheating action t1～t2, is than starting lower operating frequency f3 in action t2～t3 in operating stably t3～t4.In addition, the output of sequential control portion 41 is not limited to pwm signal, as long as making the signal of the both end voltage variation of controlling electricity consumption container C 103 just passable.Make the resonance frequency of the resonant circuit that operating frequency f1～f3 forms than discharge lamp La and resonant structure 22 high, operating frequency f1～f3 is lower, from resonant structure 22, the electric power of discharge lamp La output is more increased.That is, by the stage of operating frequency f1～f3 as described above, decline, to interim the increasing of output power of discharge lamp La.In addition, the timing t 3 that starts to start the timing t 2 of action t2～t3 and start operating stably t3～t4 for example determines by timing respectively, and the duration of preheating action t1～t2 and the duration that starts action t2～t3 are roughly respectively necessarily.

And then present embodiment has the abnormal judging part 61 that determines whether to make the abnormality that drive division 31 stops.In the example of Fig. 2, abnormal judging part 61 entirety are located at the outside of controlling with integrated circuit 4, but also can be by integrated a part for the circuit element of the abnormal judging part 61 of formation to controlling with in integrated circuit 4.In addition, controlling with in integrated circuit 4, be provided with and be judged as YES the stop control unit 42 that enforcement division 34 is at least indicated stopping of drive division 31 and sequential control portion 41 is stopped that stopping to driving integrated circuit 3 should make state that drive division 31 stops time when abnormal judging part 61.Stop control unit 42 forms the control part in technical scheme together with sequential control portion 41.From controlling with the stop control unit 42 of integrated circuit 4 to driving the circuit that stops enforcement division 34 with integrated circuit 3 to be connected to the circuit of controlling voltage vcc 1 via resistance 51.Stop control unit 42 is made as by the current potential of foregoing circuit the L level equating with earthing potential conventionally, when drive division 31 is stopped, by the current potential of foregoing circuit being made as and controlling the H level that voltage vcc 1 equates and indicate stopping of drive division 31.That is, during being instructed to the stopping of drive division 31 in above-mentioned resistance R 51 not current flowing and power consumption not, power consumption reduces compared with always making in above-mentioned resistance R 51 structure of current flowing.In Fig. 1, in the timing shown in Fig. 4, the output of stop control unit 42 (stopping the input of enforcement division 34) becomes H level, and the output that stops thus enforcement division 34 becomes L level, and the action of oscillating portion 35 and drive division 31 is stopped respectively.

As abnormal judging part 61, be judged as the state of abnormality, can consider not connect the no-load condition of discharge lamp La on resonant structure 22.Abnormal judging part 61 like this can be realized by known technology, so diagram and detailed explanation are omitted.

Here, in operating stably t3～t4, power supply is disconnected the in the situation that then horse back being such by power turn-on, by the moment of power turn-on, if it is insufficient to control the electric discharge of electricity consumption container C 103, the output power of resonant structure 22 is temporary after the firm conducting of power supply as described above exceedingly becomes large, acts on excessive electric stress forming on the circuit element of resonant structure 22 or discharge lamp La.

So, in the present embodiment, stopped enforcement division 34 before the dwell time T1 through regulation from the output of controlling voltage vcc 1 starts, output is made as to L level and drive division 31 is stopped, after through dwell time T1, output is made as to H level and starts the action of drive division 31.This dwell time T1 is made as to the time of the electric discharge of enough control electricity consumption container C 103.Thereby, even horse back is by situation such power turn-on after power supply being disconnected in operating stably t3～t4 as described above, owing to having carried out controlling the electric discharge of electricity consumption container C 103 in dwell time T1 when starting, so also can avoid acting on excessive electric stress on the circuit element of resonant structure 22 and discharge lamp La.

In addition, in the example of Fig. 1, till t4 when controlling the output of voltage vcc 1 and start to play the end of operating stably t3～t4, to be maintained L level to the input (being the output of stop control unit 42) that stops enforcement division 34, thus starting preheating starting after through dwell time T1 and move t1～t2 from controlling the output of voltage vcc 1, but after the output of control voltage vcc 1 starts, to the input that stops enforcement division 34, becoming H level is then changed to L level, from start preheating action t1～t2 after through dwell time T1 to the input of Stopping practice portion 34 becomes L level.; strictly say; from control power supply unit 33 output control voltage vccs 1 and to the input that stops enforcement division 34, be L level state continuance moment of dwell time T1 start preheating action t1～t2, finishing at least to have guaranteed stopping of dwell time T1 to during then starting preheating action t1～t2 from operating stably t3～t4.

In addition, in the stopping of drive division 31, nonsensical to the output of oscillating portion 35 from sequential control portion 41.So, sequential control portion 41 also can by and stop transmitting-receiving or the timing of the signal of telecommunication between enforcement division 34, in the stopping of drive division 31, do not generate the signal of telecommunication (being pwm signal) of inputting to oscillating portion 35 in above-mentioned example.If adopt this structure, can realize the minimizing of the power consumption in the stopping of drive division 31, relaxed the requirement for the durability of the circuit element of startup portion 32 etc. thereupon, can realize thus the miniaturization driving with integrated circuit 3.

(execution mode 2)

The basic structure of present embodiment and execution mode 1 are common, so give identical label and description thereof is omitted for common part.

Present embodiment as shown in Figure 7, possesses for the transducer 62 of human body and according to the human body judging part 43a that has or not the existence of human body in the detection range of the output judgement regulation of this transducer 62.That is, by transducer 62 and human body judging part 43a, form so-called human body sensor.Human body judging part 43a is located at and controls with in integrated circuit 4, and transducer 62 and human body judging part 43a will control voltage vcc 1 as power supply.As transducer 62, for example, can use the thermoelectric pickup detecting from the hot line (infrared light) of human body radiation, because transducer 62 and human body judging part 43a can both realize by known technology, so detailed diagram and explanation are omitted.

In the present embodiment, sequential control portion 41 starts lighting a lamp of discharge lamp La by a series of action from preheating action when having judged existing of human body by human body judging part 43a.In addition, passed through lighting a lamp during the retention time of regulation not determined rising of human body by human body judging part 43a, stop control unit 42, by output being made as to H level and the output of sequential control portion 41 being stopped, being turned off the light discharge lamp La.

According to said structure, can suppress to forget because of user the meaningless power consumption that operation that discharge lamp La is turned off the light causes.

(execution mode 3)

The basic structure of present embodiment and execution mode 1 are common, so give identical label and description thereof is omitted for common part.

Present embodiment as shown in Figure 8, possesses the known lightness transducer 63 of the lightness that detects the space of being thrown light on by discharge lamp La, controlling with in integrated circuit 4, be provided with the adjusting control part 44 that at least generates the output corresponding with the output of lightness transducer 63 in the operating stably of sequential control portion 41.As shown in Figure 9, regulate control part 44 to be connected to and to control in electricity consumption container C 103 via resistance, by making to control the both end voltage of electricity consumption container C 103, change and carry out control action frequency equally with sequential control portion 41.In the present embodiment, regulate control part 44 output pwm signal same with sequential control portion 41, but also pwm signal not necessarily of the output of adjusting control part 44, as long as making the signal of the two ends variation of controlling electricity consumption container C 103 just passable.

In addition, switch portion 21 has the detection being connected between switch element Q20 and earthing potential resistance R3 in order to detect the electric current in the switch element Q20 that flows through low voltage side (downside).

And then, in the oscillating portion 35 driving with integrated circuit 3, impose variation, so that it detects the output of the current value with resistance R3 (being switch element Q20 and the current potential detecting with the tie point of resistance R3), sequential control portion 41 and regulate the output of control part 44 to regulate operating frequency according to flowing through.That is, by sequential control portion 41, stop control unit 42 and adjusting control part 44, form the control part in technical scheme.

If explained, in oscillating portion 35, replace voltage follower OP1 and be provided with input operational amplifier OP3.This input is transfused to the both end voltage of controlling electricity consumption container C 103 in non-reversion input terminal with operational amplifier OP3, and the detection resistance R3 that is transfused to switch portion 21 via resistance R 109 in reversion input terminal and the voltage (hereinafter referred to as " current detection voltage ") of the tie point of switch element Q20, and lead-out terminal is connected via capacitor C104 with the input terminal that reverses and forms integrating circuit.Input, is connected to and controls on the reversion input terminal of using operational amplifier OP2 via resistance R 110 and make the diode D102 of negative electrode towards input operational amplifier OP3 side with the lead-out terminal of operational amplifier OP3.That is, control the higher input of integrated value of the both end voltage of electricity consumption container C 103 and the difference of current detection voltage and use the output voltage of operational amplifier OP3 higher, control thus the output voltage step-down with operational amplifier OP2, operating frequency step-down.Sequential control portion 41 is same with execution mode 1 to be connected to and to control in electricity consumption container C 103 via resistance R 103, regulates control part 44 also via other resistance R 31, to be connected to and to control in electricity consumption container C 103.

Utilize Figure 10 that the action of present embodiment is described.If start the supply of the control voltage vcc 1 shown in Figure 10 (a),, after the stipulated time shorter than dwell time T1, regulate control part 44 first to start action.The output of the adjusting control part 44 shown in Figure 10 (b) is t3 when the end of action t2～t3 from starting to regulate the action of control part 44 till starting, have nothing to do and duty ratio is made as to 1 with the output of lightness transducer 63, in operating stably, t3～t4 is made as the duty ratio corresponding to the lightness being detected by lightness transducer 63.The output of the sequential control portion 41 shown in Figure 10 (c) was made as 0 by duty ratio before the zero hour that starts action t2～t3, duty ratio is made as than 1 little and be not 0 value starting in action t2～t3, in operating stably, t3～t4 is made as 1 by duty ratio.T2 when starting the beginning of action t2～t3, the both end voltage of the control electricity consumption container C 103 shown in Figure 10 (d) rises by the output of sequential control portion 41, and the operating frequency shown in Figure 10 (e) declines thus.In addition, t3 when the beginning of operating stably t3～t4, compared with the contribution of the rising of the duty ratio of the output of sequential control portion 41, the contribution of the minimizing of the duty ratio of adjusting control part 44 is larger, the both end voltage of controlling thus electricity consumption container C 103 declines, but in the example of Figure 10, the contribution of the decline of current detection voltage is larger than the low contribution of the both end voltage of control electricity consumption container C 103, operating frequency declines thus, and the variation of operating frequency as a whole becomes same with the example of the Fig. 1 shown in execution mode 1.

As the action of t3～t4 in operating stably, the lightness particularly for example being detected by lightness transducer 63 is brighter, more reduce the duty ratio of the output that regulates control part 44 and operating frequency is uprised, the output power from resonant structure 22 to discharge lamp La reduces.By above-mentioned action, can when maintaining the lightness comprising from the light (so-called exterior light) of the light source beyond discharge lamp La, suppress power consumption.

In addition, if only make the light of discharge lamp La incide in lightness transducer 63, also can carry out haveing nothing to do with outer light and the light output of discharge lamp La being maintained to certain control.

In addition, circuit structure is not limited to the structure of Fig. 9, for example in control electricity consumption container C 103, do not connect and regulate control part 44, and on the control operational amplifier OP2 that is connected to oscillating portion 33 via voltage follower OP1 same with the example of the Fig. 5 shown in execution mode 1, on the other hand, about regulating control part 44, as shown in figure 11, also can the adjusting electricity consumption container C 31 that both end voltage is changed according to the output that regulates control part 44 be additionally set with control electricity consumption container C 103.Regulate the control electricity consumption container C 103 in the example of electricity consumption container C 31 and Fig. 9 same, one end is connected to input with being connected to and regulating on control part 44 on the non-reversion input terminal of operational amplifier OP3 and via resistance R 107, other end ground connection, resistance R 108 is also being connected in parallel.In addition, in Figure 11, omitted the diagram of controlling resistance R 103, R104 and the voltage follower OP1 of electricity consumption container C 103 and periphery thereof.About the part beyond above-mentioned, be common with the example of Fig. 9, about diagram and the explanation of common part, omit.In the case, when design, need to consider to make to regulate also among dwell time T1s fully electric discharge same with control electricity consumption container C 103 of electricity consumption container C 31.But the example of Fig. 9 has advantages of and can reduce parts number of packages compared with the example of Figure 11.

Here, in the circuit of Fig. 9 and the circuit of Figure 11, as shown in Figure 12 (a), Figure 12 (b), the input voltage Vop-cyclical movement to input with the reversion input terminal of operational amplifier OP3.As shown in Figure 12 (a), as long as enough high with respect to the input voltage Vop+ of the non-reversion input terminal to input operational amplifier OP3 by the higher limit of the input voltage Vop-of the reversion input terminal of operational amplifier OP3 to input, just as shown in figure 13, the output power (hereinafter referred to as " lamp electric power ") from resonant structure 22 to discharge lamp La is with respect to the input voltage Vop+ monotone increasing with the non-reversion input terminal of operational amplifier OP3 to input.But, during temperature is very high around high temperature or during the low-down low temperature of environment temperature, due to the variation of the characteristic of discharge lamp La, the output power deficiency of driving power portion 5, the control that lamp electric power is increased according to current detection voltage becomes and does not catch up with.For example, as shown in Figure 12 (b), becoming to the higher limit of the input voltage Vop-of the reversion input terminal of input operational amplifier OP3 always during the low temperature of the state lower than the input voltage Vop+ of the non-reversion input terminal to input operational amplifier OP3 etc., in the case of input with the output voltage of operational amplifier OP3 become higher than the output voltage of controlling use operational amplifier OP2, input no longer reflects operating frequency with the output of operational amplifier OP3, operating frequency is fixed on the lower frequency limit of regulation with haveing nothing to do with the variation (being the variation of current detection voltage) of the input voltage Vop-of the reversion input terminal of operational amplifier OP3 to input.Thus, in the present embodiment, lamp electric power is as used in Figure 14 as shown in curve PLa, as long as environment temperature is to be just maintained necessarily by the variation of operating frequency in prescribed limit, when low temperature or during high temperature, by operating frequency being fixed as to above-mentioned lower frequency limit, along with environment temperature is left and reduces from afore mentioned rules scope.Thereby, output current (hereinafter referred to as " lamp current ") from from resonant structure 22 to discharge lamp La is as used Figure 14 as shown in curve ILa, environment temperature is left and is increased from the central authorities of afore mentioned rules scope as a whole, but when low temperature or during high temperature by as described above operating frequency being fixed, compared with in the time of within the scope of being afore mentioned rules with environment temperature thus, the recruitment that the variation of environment temperature brings tails off.That is, in the present embodiment, the lost of life of the discharge lamp La that the excessive increase of the lamp current in the time of can preventing low temperature or during high temperature causes.

(execution mode 4)

The basic structure of present embodiment and execution mode 3 are common, so give identical label and description thereof is omitted for common part.

Present embodiment replaces the lightness transducer 63 of execution mode 3 and possesses as shown in Figure 15 and be transfused to the dim signal input part 64 of the light of discharge lamp La being exported to the dim signal of indicating, regulate control part 44 to move in operating stably, so that according to the light exporting change that is input to dim signal in dim signal input part 64 and makes discharge lamp La.Dim signal input part 64 is same with the transducer 62 of execution mode 2, and the control voltage vcc 1 that control power supply unit 33 is exported is as power supply.In addition, in control, use in integrated circuit 4, be provided with dim signal judging part 43f, this dim signal judging part 43f judgement is input to the kind of the dim signal in dim signal input part 64, and if the dim signal being input in dim signal input part 64 is that the signal that pilot light is exported is input to the signal of telecommunication of the content corresponding to dim signal in adjusting control part 44, if the dim signal being input in dim signal input part 64 is the signal that indication is lit a lamp or turned off the light, the signal of telecommunication of the content corresponding to dim signal is input in stop control unit 42.

General dim signal is the pwm signal transmitting via the holding wire being connected on dim signal input part 64, frequency is 100Hz～1kHz, is the higher light output of the higher indication of duty ratio, the signal of turning off the light of indicating discharge lamp La by the duty ratio below the lower limit of regulation.In addition, dim signal is not limited to the above, can be also the digital signal of exporting the analog signal of corresponding magnitude of voltage or exporting by numerical data pilot light with the light of indication.In either case dim signal input part 64 and dim signal judging part 43f can both realize by known technology, so detailed explanation and diagram are omitted.By said structure, can carry out lighting a lamp/turning off the light and the control such as the change of light output according to the discharge lamp La that carries out from outside dim signal.In addition, at dim signal judging part 43f, for example by A/D, convert during in the case of the accepting of the input from dim signal input part 64 etc. and power consumption, the conducting control of discharge lamp La is by carrying out beyond dim signal, if dim signal judging part 43f does not does not accept the input from dim signal input part 64 when starting during to the beginning of operating stably, always accept compared with the situation of the input of dim signal input part 64 and can reduce power consumption with controlling with integrated circuit 4.

Here, control the clock portion 45 with integrated circuit 4 with generated clock signal, the frequency (hereinafter referred to as " clock frequency ") of the clock signal that clock portion 45 generates is higher, faster with the action of the each portion beyond clock portion in integrated circuit 4 45 in control, for faster with the response of the input of abnormal judging part 61 grades of integrated circuit 4 outsides from control, control on the other hand the more increase of power consumption with integrated circuit 4.

And, in the present embodiment, in view of do not need especially the speed of response as described above in the stopping of drive division 31, adopted in the stopping of drive division 31 at least than the structure that in the lighting a lamp of discharge lamp La, clock frequency is reduced.

If explained, in driving, with being provided with in integrated circuit 3, report power supply unit 30, report power supply unit 30 during stopping enforcement division 34 drive division 31 moved, from the output of the control voltage vcc 1 shown in Figure 16 (a) starts, pass through dwell time T1 after and from stopping enforcement division 34, to shown in Figure 16 (b) of drive division 31 or startup portion 32, be output as H level, as shown in Figure 13 (d), produced during the output of drive division 31, as shown in Figure 16 (c), export the report voltage vcc 3 of regulation.In the present embodiment, oscillating portion 35 will report that voltage vcc 3 is as power supply, stop enforcement division 34 when above-mentioned output is made as to L level by by report voltage vcc 3 input stop, oscillating portion 35 and drive division 31 stop respectively thus.

And then above-mentioned report voltage vcc 3 is also imported into be controlled with in the clock portion 45 of integrated circuit 4.Clock portion 45, as shown in Figure 16 (e), makes not input the clock frequency TA reporting during voltage vcc 3 and reports that than having inputted the clock frequency TB during voltage vcc 3 is low.Thus, realized in the stopping of drive division 31, make the action of clock frequency ratio drive division 31 in low action.

According to said structure, thereby by making clock frequency step-down can reduce power consumption before the action of drive division 31 starts, thereby and can accelerate for the response from controlling with the outside input of integrated circuit 4 by least clock frequency being uprised in the lighting a lamp of discharge lamp La.

In addition, as long as clock frequency is just passable in the middle raising of lighting a lamp of discharge lamp La, so clock portion 45 improves the timing of clock frequency, be not limited to the timing (while being pre-thermally operated beginning) that the input of report voltage vcc 3 as described above starts, before the beginning of the operating stably (time), just can when starting the end of action.

In addition, in the control of present embodiment, use in integrated circuit 4, during can identifying drive division 31 and move by report voltage vcc 3, so also can make sequential control portion 41 in (being during drive division 31 stops) during not inputting report voltage vcc 3, regulate control part 44 not generate to the output of oscillating portion 35.If adopt this structure, with sequential control portion 41 and regulate control part 44 also to generate in the stopping of drive division 31 to compared with the situation of the output of oscillating portion 35, can realize the minimizing of the power consumption in the stopping of drive division 31, relax the requirement for the durability of the circuit element of startup portion 32 etc. thereupon, can realize thus the miniaturization driving with integrated circuit 3.

(execution mode 5)

The basic structure of present embodiment and execution mode 4 are common, so give identical label and description thereof is omitted for common part.

Present embodiment is compared with execution mode 4, dim signal input part 64 is not set, replace, as shown in figure 17, possess the light a lamp timing portion 46 of time timing of the accumulative total of discharge lamp La, regulate control part 44 according to being lit a lamp the time by the accumulative total of timing portion 46 timing, duty ratio in operating stably is increased gradually, with make up with accumulative total light a lamp the discharge lamp La that the process of time accompanies light beam low and make take 100% as the upper limit, to rise gradually with respect to the ratio (hereinafter referred to as " light modulation ratio ") of the rated electrical of discharge lamp La to the output power of discharge lamp La.Thus, playing light modulation from the use that starts discharge lamp La than during reaching 100%, the light beam of discharge lamp La can be remained roughly certain.More particularly, for example as shown in figure 18, when the accumulative total time of lighting a lamp is 0, light modulation ratio is made as to 70%, before light modulation ratio reaches 100%, makes light modulation than rising with linearity with respect to the accumulative total time of lighting a lamp, after light modulation ratio reaches 100%, light modulation ratio is maintained to 100%.In the example of Figure 18, make light modulation longer than time rated life time of discharge lamp La than the accumulative total that reaches 100% time of lighting a lamp.As lighting a lamp Time dependent light modulation than the action of (strictly saying it is the duty ratio that regulates the output of control part 44) according to adding up, both can keep in advance representing totally to light a lamp the time with the tables of data of the relation of light modulation ratio and by realizing by this tables of data controlling in the such memory of for example storage part 47 described later that have with integrated circuit 4, also can realize by computing.

And then, timing portion 46 is accumulative total timing service time to the service time as discharge lamp ignition device self also, for example, if reach time device lifetime (10 years) as the regulation in life-span of discharge lamp ignition device service time by the accumulative total of timing portion 46 timing, stop control unit 42, by being made as H level to driving with the output that stops enforcement division 34 of integrated circuit 3, stops the action of drive division 31.Thus, can prevent abnormal heating of bringing because of the life-span of circuit element etc.

Be described more specifically the structure that accumulative total is lit a lamp the time and added up timing service time.Control and there is the storage part 47 being formed by nonvolatile memory with integrated circuit 4, the time and totally leaving in storage part 47 service time of accumulative total being lit a lamp in during discharge lamp La turns off the light.Timing portion 46 when starting, for example start preheating action before, read in the accumulative total leaving in storage part 47 and light a lamp time and accumulative total service time, start the timing that accumulative total is lit a lamp time and accumulative total service time.As accumulative total, light a lamp the time, in the time of both can be to the length gauge of the time of input report voltage vcc 3, also can be when carrying out the length gauge of time of operating stably.As accumulative total service time, when for example inputting the length gauge of time of report voltage vcc 3.In which kind of situation, all when power supply is disconnected, timing portion 46 is written to light a lamp time and accumulative total of the accumulative total in timing respectively in storage part 47 service time.In addition, add up service time owing to representing the service time of discharge lamp ignition device self, thus be not reset, and the accumulative total time of lighting a lamp needs reset (returning to 0) when having changed discharge lamp La.As the timing that the time of lighting a lamp resets by accumulative total, the time of for example both can when no-load condition being detected, accumulative total having been lit a lamp resets, also the switch (not shown) operating in the time of can being arranged on the replacing of discharge lamp La, the time of when having operated this switch, accumulative total being lit a lamp resets.

Here, in accumulative total is lit a lamp time or accumulative total are written to storage part 47 service time before, need to delete service time remaining on light a lamp time or accumulative total of accumulative total in storage part 47.And, general writing of memory fashionable and power consumption respectively while deleting, so make to delete and write mutually continuous in the situation that, the time that the temporary change of power consumption is large is elongated.So, by remaining on the timing that the data (hereinafter referred to as " ephemeral data ") such as time and accumulative total service time delete of lighting a lamp of accumulative total in storage part 47 during the data of using at stop control unit 42 and in regulating the action of control part 44 are during power supply is disconnected, separate with the timing that writes ephemeral data, this can shorten in order to carry out the deletion to storage part 47 and to write and during large each of the temporary change of power consumption, so be preferred.As ephemeral data as described above, except accumulative total, light a lamp time and accumulative total service time, it will also be appreciated that power supply is switched on the number of times of disconnection and light modulation that discharge lamp La is turned off the light before tight is compared etc.

And then, for the deletion of storage part 47 and the processing that writes etc. from shortening the viewpoint of the time that the above-mentioned processing of storage part 47 is spent, preferably not clock frequency is carried out in during making clock frequency higher compared with carrying out in during low.

More than comprehensive, in the present embodiment, when the timing that deletion accumulative total is lit a lamp to the time and added up service time is made as the beginning of operating stably.In addition, even if clock portion 45, in the supply that had been stopped report voltage vcc 3 before having write of storage part 47, did not make clock frequency step-down before having write of storage part 47 yet.The above-mentioned action of clock portion 45 both can realize by the control of timing portion 46, also can higher clock frequency be maintained enough to the structure of stipulated time writing of storage part 47 and be realized by making after report the stopping of voltage vcc 3 clock portion.Present embodiment is passed through said structure, with to the deletion of storage part 47 with write the situation of mutually carrying out continuously and during making clock frequency lower in carry out the deletion to storage part 47 and situation about writing is compared, the large time of the temporary change of power consumption is shortened, reduced the electric stress that acts on driving power portion 5 grades.

(execution mode 6)

The basic structure of present embodiment and execution mode 5 are common, so give identical label for common part, omit diagram and explanation.

Present embodiment as shown in figure 19, possess output with by the power supply test section 165 of the direct voltage corresponding voltage of the output voltage smoothing of rectification part DB.In addition, the output of enforcement division 34 based on power supply test section 165 that stops of present embodiment judges low from the voltage (hereinafter referred to as " input supply voltage ") of AC power AC input, when being judged as input supply voltage when low, same while becoming H level with the output of stop control unit 42 output is made as to L level, drive division 31 and report power supply unit 30 are stopped.

If specifically described, power supply test section 165 as shown in figure 20, output by the output voltage of rectifier DB with divider resistance dividing potential drop and with capacitor level and smooth direct voltage.In addition, stop enforcement division 34 and possess the 5th reference voltage Vr5 that is transfused to regulation in non-reversion input terminal and the input comparator CP4 that is transfused to the output voltage of power supply test section 165 in reversion input terminal, non-reversion input terminal is connected on stop control unit 42 and in reversion input terminal, is transfused to the input comparator CP5 of the 5th reference voltage Vr5, export above-mentioned two input comparator CP4, the logic of the output of CP5 and logic and circuit OR2, by being located at, drive the constant current source Ir2 charging by the outside delay electricity consumption container C 105 of integrated circuit 3, by the FET of n channel-type, form and be connected to side by side the switch element Q106 that postpones in electricity consumption container C 105 and be transfused to the output of logic and circuit OR2 in grid, and on non-reversion input terminal connection delay electricity consumption container C 105 and be transfused to the output comparator CP6 of the 6th reference voltage Vr6 of regulation in input terminal in reversion.This output comparator CP6 is output as during H level during drive division 31 and report power supply unit 30 move, during output report voltage vcc 3.

The above-mentioned action that stops enforcement division 34 is described.Stop enforcement division 34 by using from controlling the control voltage vcc 1 exported of power supply unit 33 as power supply, when starting, make to postpone the charging of electricity consumption container C 105 starts together with starting from the output of control voltage vcc 1 of controlling power supply unit 33, when the both end voltage of delay electricity consumption container C 105 has reached the 6th reference voltage Vr6, by the output of output comparator CP6, become H level, start the action of drive division 31 and the output of report voltage vcc 3, now, in startup portion 32, switch element Q101 is fixed to off-state.That is, will postpone the capability value and the product of the 6th reference voltage Vr6 of electricity consumption container C 105, remove and the charging interval T2 (with reference to Figure 21) that obtains is consistent with dwell time T1 with the output current of constant current source Ir2 that stops enforcement division 34.

In addition, at the output voltage of power supply test section 165 lower than being output as H level the 5th reference voltage Vr5 or at stop control unit 42, by the output of any input comparator CP4, CP5, become H level and by switch element Q106 conducting, via switch element Q106, will postpone electricity consumption container C 105 thus discharges sharp, lower than the 6th reference voltage Vr6, the output of output comparator CP6 becomes L level to the both end voltage of delay electricity consumption container C 105, carries out thus stopping of drive division 31 and report voltage vcc 3.Here, time (hereinafter referred to as " the retention time ") T3 (with reference to Figure 21) that becomes L level from switch element Q106 being disconnected to the output of output comparator CP6 becomes enough short.

In Figure 21, represent an example of the action of present embodiment.In the example of Figure 21, in the output of the stop control unit 42 shown in Figure 21 (a), become the moment of L level, the output voltage of the power supply test section 165 shown in Figure 21 (b) is lower than the 5th reference voltage Vr5, the output of an input comparator CP4 shown in Figure 21 (c) is H level thus, thereby the output of the logic shown in Figure 21 (d) and circuit 2 also becomes H level.If the output voltage of final power supply test section 165 exceedes the 5th reference voltage Vr5, the output of logic and circuit OR2 becomes L level and switch element Q106 is disconnected, and starts thus to postpone the charging of electricity consumption container C 105.And then, if through charging interval T2, the both end voltage that postpones electricity consumption container C 105 reaches the 6th reference voltage Vr6, and the output of output comparator CP6 becomes H level, the output of the report voltage vcc 3 shown in action and Figure 21 (f) of beginning drive division 31.Then, if the output voltage of power supply test section 165 decline and lower than the 5th reference voltage Vr5, in very short retention time T3, the output of output comparator CP6 becomes L level, here, the output of the action of drive division 31 and report voltage vcc 3 is stopped respectively.

In addition, in the control of present embodiment, with in integrated circuit 4, when starting to report the input of voltage vcc 3, start to move a series of action of operating stably from preheating.

In addition, power supply test section 165 and the structure that stops enforcement division 34 are not limited to the above, for example as shown in figure 22, also can adopt following structure: in power supply test section 165, append the switch element being formed by the transistor of the npn type of the charging voltage that is transfused to capacitor in base stage, grounded emitter, and the collector electrode of this switch element is connected on the non-reversion input terminal of the input comparator CP5 common with stop control unit 42.That is, power supply test section 165 according to by the output voltage of rectification part DB by electric resistance partial pressure and by capacitor level and smooth voltage with respect to the high or low exporting change that makes of conducting voltage of switch element.Select to form each element of power supply test section 165 so that the output voltage of proper rectification part DB when enough high by the switch element conducting of power supply test section 165 if the low state of input voltage of the output voltage deficiency of rectification part DB disconnects the switch element of power supply test section 165.In the example of Figure 22, power supply test section 165 is upper with the output (controlling voltage vcc 1) that the tie point that stops enforcement division 34 is connected to control power supply unit 33 via resistance R 51, between resistance R 51 and stop control unit 42, has appended resistance R 52.Make by these resistance R 51, R52 high voltage ratio the 5th reference voltage Vr5 after control voltage vcc 1 dividing potential drop, even if the output of stop control unit 42 is L level, if the switch element of power supply test section 165 is disconnected by the low state of input voltage, makes the output that stops enforcement division 34 become L level and carry out stopping of drive division 31 grades.Or, also can be made as following action: if make by resistance R 51, R52 lowly by controlling voltage ratio the 5th reference voltage Vr5 after voltage vcc 1 dividing potential drop, in the output of stop control unit 42, be only that H level and the output that stops the input comparator CP5 of enforcement division 34 while being the low state of input voltage become H level and makes the output that stops enforcement division 34 become L level.In the structure of Figure 22, by the input comparator CP4 of power supply test section 165 sides in Figure 20 and logic and circuit OR2 are omitted respectively, compared with the example of Figure 20, circuit structure is simplified on the whole.Here, in the structure of Figure 22, when the output voltage of rectification part DB is enough high and the output of stop control unit 42 irrelevant and the input of the non-reversion input terminal to input comparator CP5 is fixed as to L level, so that does not carry out implementing by the output of stop control unit 42 stops, if but between power supply test section 165 and input comparator CP5, appended resistance (not shown), when the output voltage of rectification part DB is enough high, also could implement stop by the output of stop control unit 42.

(execution mode 7)

The basic structure of present embodiment and execution mode 6 are common, so give identical label for common part, omit diagram and explanation.

As shown in figure 23, in the preheating part 23 of present embodiment, between the once coiling of transformer Tr1 and earthing potential, appended switch element Q3.This switch element Q3 carries out conducting by sequential control portion 41 and disconnects control, at least in preheating action, is switched on, and at least in operating stably, is disconnected on the other hand.Thus, power consumption that can be lowly meaningless compared with the situation of switch element Q3 is not set.

In addition, in the present embodiment, using detecting as the abnormal judging part 61 of the no-load condition of abnormality, be divided into and generate according to being whether that the non-loaded test section 61a of the output that changes of no-load condition and the output based on non-loaded test section 61a judge whether it is no-load condition and by the non-loaded judging part 43b being input to corresponding to the output of judged result in stop control unit 42, by integrated non-loaded judging part 43b controlling with in integrated circuit 4.As non-loaded test section 61a, for example can use detection will be connected to the circuit of the impedance between the terminal on every one end of filament of discharge lamp La, non-loaded test section 61a and non-loaded judging part 43b can realize by known technology, so omit detailed diagram and explanation.

And then, the output of power supply test section 165 is not to stopping enforcement division 34 but inputs to control integrated circuit 4, controlling with in integrated circuit 4, be provided with output based on power supply test section 165 and judge whether it is the abnormality (hereinafter referred to as " the low state of input voltage ") of input supply voltage deficiency and by the low judging part 43c of input voltage being input to corresponding to the output of judged result in stop control unit 42.Electric power from from AC power AC to rectification part DB is supplied with to the situation (being the situation that power supply is disconnected) being stopped and be also judged as the low state of input electric power.

And, stop control unit 42 is termly with reference to the output of non-loaded judging part 43b and the output of the low judging part 43c of input electric power, if be judged as abnormality in any of non-loaded judging part 43b and the low judging part 43c of input electric power, will with the output of integrated circuit 3, be made as H level to driving, and sequential control portion 41, adjusting control part 44 and timing portion 46 are stopped respectively.The in the situation that of being judged as abnormality before pre-thermally operated beginning, by the output of stop control unit 42 is maintained to H level, do not start the action of drive division 31.In addition,, when stopping because of the judgement of no-load condition, timing portion 46 resets the accumulative total time of lighting a lamp, and the accumulative total time of lighting a lamp that there is no timing is abandoned.

(execution mode 8)

The basic structure of present embodiment and execution mode 5 are common, so give identical label for common part, omit diagram and explanation.

In the present embodiment, replace abnormal judging part 61, as shown in figure 24, be provided with and detect the parameter changing and export the life tests portion 66 corresponding to the voltage of the parameter detecting when the end of lifetime of discharge lamp La.Particularly, the asymmetrical current producing in discharge lamp La detects as above-mentioned parameter in the life tests portion 66 of present embodiment, exports the voltage corresponding with it.

In addition, in control, use in integrated circuit 4, be provided with output based on life tests portion 66 and judge whether it is the end of lifetime state of the abnormality that is end of lifetime as discharge lamp La, and by the discharge lamp judging part 43d being input to corresponding to the output of judged result in stop control unit 42.

If explained, as shown in figure 25, life tests portion 66 possesses that the inductor L1 that one end is connected to resonant structure 22 via a filament of resistance R 111 and discharge lamp La is upper, the capacitor C106 of other end ground connection and the parallel circuits of resistance R 113.In addition, capacitor C106 is upper via making negative electrode be connected to discharge lamp judging part 43d towards the diode D103 of capacitor C106, and the tie point of this diode D103 and discharge lamp judging part 43d is connected on the output (controlling voltage vcc 1) of controlling power supply unit 33 via resistance R 112.

Here, in the situation that discharge lamp La is not end of lifetime, in the lighting a lamp of discharge lamp La, electric current (hereinafter referred to as " the inflow current ") Idc+ from resonant structure 22 to life tests portion 66 and the electric current from life tests portion 66 to resonant structure 22 (hereinafter referred to as " outflow electric current ") Idc-are mutually roughly equal.Thus, the both end voltage of the capacitor C106 of life tests portion 66, the output voltage of life tests portion 66 is maintained roughly certain voltage (hereinafter referred to as " normal voltage "), and this normal voltage is about the voltage of controlling after voltage vcc 1 use resistance R112, R113 dividing potential drop.In addition, the inductor L1 of resonant structure 22 and the tie point of discharge lamp La are connected to via resistance R 114 on the output of high-voltage side of DC power supply portion 1.

On the other hand, if discharge lamp La becomes end of lifetime, the consumption that is coated in the emitter on filament in discharge lamp La produces difference in each filament, one of above-mentioned electric current I dc+, Idc-becomes than another large (producing asymmetrical current), between the output voltage and above-mentioned normal voltage of life tests portion 66, there is poor corresponding to above-mentioned electric current I dc+, Idc-poor (size of asymmetrical current).For example, in the situation that outflow electric current I dc+ is more than inflow current Idc-, it is higher than above-mentioned normal voltage that the output voltage of life tests portion 66 becomes, otherwise in the situation that outflow electric current I dc+ is fewer than inflow current Idc-, the output voltage of life tests portion 66 becomes than above-mentioned normal electrical and forces down.

Discharge lamp judging part 43d by the output voltage of life tests portion 66 with than the lower voltage limit of the high set upper limit voltage of normal voltage and the regulation forced down than normal electrical, compare respectively, if the output voltage of life tests portion 66 to be upper voltage limits following and lower voltage limit above, be judged as and be not end of lifetime state, if the output voltage of life tests portion 66 exceedes upper voltage limit or lower than lower voltage limit, be judged as end of lifetime state.For example, controlling voltage vcc 1, be 5V, normal voltage be 2.5V in the situation that, upper voltage limit is made as to 4V and lower voltage limit is made as to 1V.

If stop control unit 42 is judged as end of lifetime state by discharge lamp judging part 43d, will with the output of integrated circuit 3, be made as H level to driving, driving drive division 31 grades of integrated circuit 3 are stopped, and make sequential control portion 41 and regulate control part 44 to stop respectively.

And then, according to whether connecting the filament of discharge lamp La in the resistance R 111 in life tests portion 66, whether be no-load condition, the both end voltage difference of the capacitor C106 of life tests portion 66.Thereby, also can the detection (judgement) for no-load condition by the output of life tests portion 66.But, owing to also considering before the action of drive division 31 starts, also flowing in the capacitor C106 of life tests portion 66 via resistance R 114 and preheat circuit 23 from the electric current of DC power supply portion 1, so in the case of the output of life tests portion 66 is used for the detection of no-load condition, the undetected survey that the charging of the capacitor C106 under electric current as described above causes need to make the time constant of life tests portion 66 shorter than dwell time T1, at least can not occurred after the action of drive division 31 starts.

(execution mode 9)

The basic structure of present embodiment and execution mode 6 are common, so give identical label for common part, omit diagram and explanation.

The DC power supply portion 1 of present embodiment as shown in figure 26, is known so-called boost chopper (booster converter).Particularly, possess on the tie point that the inductor L2 of (being between the DC output end and earthing potential of high-voltage side of rectification part DB) and the series circuit of diode D1 and output capacitor C6 between the DC output end that is connected to rectification part DB and one end be connected to inductor L2 and diode D1 and the switch element Q4 of other end ground connection and the series circuit of resistance R 5, using the both end voltage of output capacitor C6 as output voltage, the Duty ratio control output voltage of the switch element Q4 disconnecting by periodicity conducting.Generally, if use the such Switching Power Supply of booster converter, due to the improvement of power factor, power consumption reduces.

And then, the DC power supply test section 167 of the voltage that present embodiment for example possesses by the divider resistance of the output voltage dividing potential drop of DC power supply portion 1 is formed, the higher output of output voltage of DC power supply portion 1 is higher.In addition, as power supply test section 165, as the example of Figure 20, use the higher unit of exporting higher voltage of effective value of the output voltage of rectification part DB.

In addition, in the driving of present embodiment, use in integrated circuit 3, be provided with the circuit of the switch element Q4 for driving DC power supply portion 1.If explained, in driving, use in integrated circuit 3, be provided with the voltage mistake amplifier OP4 of output corresponding to the difference of the 7th reference voltage Vr7 of regulation and the output voltage of DC power supply test section 167, by the multiplier 36a of the output multiplication of the output of power supply test section 165 and wrong amplifier OP4, in reversion, be transfused to the output of multiplier 36a in input terminal but not reversion input terminal is connected to the comparator C P7 on the switch element Q4 of DC power supply portion 1 and the tie point of resistance R 5, in reseting terminal, be transfused to the flip-flop circuit 36b of the output of comparator C P7, and it is upper and according to the output of flip-flop circuit 36b, the switch element Q4 conducting of DC power supply portion 1 is disconnected the 36c of power drives portion driving via resistance R 4, to be connected to the switch element Q4 of DC power supply portion 1.

And then, on the inductor L2 of DC power supply portion 1, being provided with 2 coilings of one end ground connection, the other end of these 2 times coilings is connected to be located at and drives with on the 36d of zero current detection portion in integrated circuit 3.The 36d of zero current detection portion is connected to arranging on terminal of flip-flop circuit 36c, voltage based on induction in above-mentioned 2 coilings detects the exergonic of inductor L2 and completes, and to flip-flop circuit 36b when exergonic the completing of inductor L2 being detected terminal input pulse is set.

Thus, the switch element Q4 of DC power supply portion 1 is periodically carried out to conducting and disconnect driving, its duty ratio of FEEDBACK CONTROL, so that the output voltage of DC power supply portion 1 becomes the target voltage of regulation.This target voltage is to make the output voltage of DC power supply test section 167 become the voltage of the 7th reference voltage Vr7.

And then, in driving, with in integrated circuit 3, the output being provided with based on DC power supply test section 167 judges whether the abnormality (hereinafter referred to as " the low state of direct voltage ") of the output voltage deficiency that is DC power supply portion 1 and exports the low judging part 37 of direct voltage corresponding to the voltage of judged result.If specifically described, the low judging part 37 of direct voltage as shown in figure 27, possesses and in non-reversion input terminal, is transfused to the output voltage of DC power supply test section 167 and is transfused in reversion the switch element Q107 that the FET by n channel-type on the lead-out terminal that the comparator C P8 of the 8th reference voltage Vr8 of the regulation lower than the 7th reference voltage Vr7 and grid be connected to this comparator C P8 forms in input terminal.One end ground connection of this switch element Q107 and in the other end via resistance R 32 be transfused to report voltage vcc 3, the tie point of this switch element Q107 and resistance R 32 as the output of the low judging part 37 of direct voltage be connected to control use integrated circuit 4 on.Above-mentioned the 8th reference voltage Vr8 is made as 50%～80% of the 7th reference voltage Vr7 corresponding with target voltage.; the low judging part 37 of direct voltage when the output voltage of DC power supply test section 167 be that the 8th reference voltage Vr8 is not judged as the low state of direct voltage and output is made as to L level when above; when the output voltage of DC power supply test section 167 is judged as the low state of direct voltage than the 8th reference voltage Vr8 when low, output is made as to H level.For example, in the case of make the 8th reference voltage Vr8 be the 7th reference voltage Vr7 80%, when the output voltage fall short voltage of DC power supply portion 1 approximately 80% time be judged as the low state of direct voltage.

In addition,, controlling with in integrated circuit 4, be provided with the output proper transformation of low direct voltage judging part 37 is input to the judgement input part 144 in stop control unit 42.

And then present embodiment is same with execution mode 8, possess life tests portion 66 and discharge lamp judging part 43d.

The stop control unit 42 of present embodiment is at any time with reference to the output of discharge lamp judging part 43d with judge the output of input part 144, if 43d is judged as end of lifetime state by discharge lamp judging part, to be made as H level with the output of integrated circuit 3 to driving equally with execution mode 8, driving drive division 31 grades of integrated circuit 3 are stopped, and make sequential control portion 41 and regulate control part 44 to stop respectively.

In addition, stop control unit 42 is in the situation that being judged as the low state of direct voltage by the low judging part 37 of direct voltage, not to make as described above drive division 31 and sequential control portion 41 stop immediately, but control sequence control part 41 is to restart time T 5 (with reference to Figure 29) by what start that action stipulates, if be still judged as the low state of direct voltage after restarting time T 5, in this moment, same when being judged as end of lifetime state, to with the output of integrated circuit 3, be made as H level to driving, driving drive division 31 grades of integrated circuit 3 are stopped, and make sequential control portion 41 and regulate control part 44 to stop respectively.

In Figure 28 and Figure 29, represent the action of present embodiment.In Figure 28 and Figure 29, be respectively that the time of (a) output voltage of representing DC power supply test section 167 changes, (b) represent the time of the output of the comparator C P8 of the low judging part 37 of direct voltage change, (c) represent the time of the output of the low judging part 37 of direct voltage change, time of the output of (d) order of representation control part 41 changes, (e) represent the time of operating frequency change, (f) represent that stop control unit 42 is for driving the time with the output of integrated circuit 3 to change.Figure 28 represent the low state of direct voltage (being that the low judging part of direct voltage is the state of H level) in the case of than restart the 4 interior end of the short time T of time T 5, thus do not carry out that stop control unit 42 implements stop action.In addition, Figure 29 represents that the duration of the low state of direct voltage has reached and restarts time T 5, carried out the action in situation about stopping that stop control unit 42 implements thus.In the present embodiment, driving makes the 36c of power drives portion also stop by the enforcement division 34 that stops of integrated circuit 3 when stop control unit 42 is output as H level, in Figure 29, continuing after the end of the startup action of restarting time T 5, by stopping of the 36c of power drives portion, the output voltage of the output voltage of DC power supply portion 1 and DC power supply test section 167 declines.

In addition, the in the situation that of making immediately drive division 31 and the 36c of power drives portion stop when being judged as the low state of direct voltage, the low state of direct voltage for example, because instantaneous power failure etc. cause, can not make discharge lamp La light a lamp even if eliminated at short notice.To this, in the present embodiment, by when being judged as the low state of direct voltage, startup action being restarted to time T 5 as described above, in the case of going out, the low state discharge lamp of the direct voltage La sudden strain of a muscle of short time as described above can make discharge lamp La again light a lamp.In addition, after the end of above-mentioned startup action of restarting time T 5, be judged as the low state of direct voltage drive division 31 and the 36c of power drives portion are stopped, even so in the case of for example because of the output of fault DC power supply test section 167 do not reflect the output voltage of DC power supply portion 1 be always 0V such, also can avoid by wrong FEEDBACK CONTROL the electric stress of overaction on circuit element and discharge lamp La.

In addition, the stop control unit 42 of present embodiment is in the case of judging both of end of lifetime state and the low state of direct voltage take the action judging based on the low state of direct voltage as preferential, do not carry out the action corresponding to the judgement of end of lifetime state in during being judged as the low state of direct voltage.Its reason be because, if there is the low state of direct voltage, consider for example sudden strain of a muscle of discharge lamp La of simultaneous thus to go out and lamp current is temporary becomes asymmetric and erroneous judgement is end of lifetime state, if carry out stopping of drive division 31 and the 36c of power drives portion according to such erroneous judgement, likely can not carry out in fact the startup action of the judgement based on the low state of direct voltage as described above.In addition, for example, by making operating frequency fully leave and guarantee so-called slow phase side action with respect to the resonance frequency of the resonant circuit of resonant structure 22 and discharge lamp La formation, can avoid the erroneous judgement causing that knocks out as described above, if but like this, because idle current increases, circuit loss increases, so not preferred.

(execution mode 10)

The basic structure of present embodiment and execution mode 9 are common, so give identical label for common part, omit diagram and explanation.

The 36d of zero current detection portion of present embodiment as shown in figure 30, possessing reversion input terminal, to be connected to the secondary coiling of inductor L2 of DC power supply portion 1 upper and in non-reversion input terminal, be transfused to the input comparator CP9 of the 9th reference voltage Vr9 of regulation, the single-shot trigger circuit OS that starts the output of the pulse of regulation amplitude when the output of input comparator CP9 when L level is reversed to H level, the non-inverter circuit INV of the output of output single-shot trigger circuit OS, the 1st logic integrated circuit AND1 of the logic product of the output of the output NAND circuit INV of output input comparator CP9, by the reservation electricity consumption container C 107 of charging as the constant current source Ir3 of power supply to control voltage vcc 1, by the FET of n channel-type, form and be connected in the switch element Q108 that retains in electricity consumption container C 107 and connecting the lead-out terminal of the 1st logic integrated circuit AND1 on grid in parallel, in reversion input terminal, be transfused to the 10th reference voltage Vr10 of regulation and on non-reversion input terminal, connecting the output comparator CP10 that retains electricity consumption container C 107, and the 2nd logic integrated circuit AND2 that the logic product of the output of the output of output comparator CP10 and single-shot trigger circuit OS is exported as the output of the 36d of zero current detection portion.

Utilize Figure 31 that the action of the 36d of zero current detection portion is described.The situation that consideration changes to the input voltage of the 36d of zero current detection portion from 2 coilings of the inductor L2 of DC power supply portion 1 as shown in (b) Figure 31.So the output of input comparator CP9 becomes in Figure 31 shown in (c), the output of single-shot trigger circuit OS becomes in Figure 31 shown in (e).Retain electricity consumption container C 107 is discharged sharp via switch element Q108 when the 1st logic integrated circuit AND1 is output as H level, so during the output L of the 1st logic integrated circuit AND1 level, during input comparator CP9 is output as L level and single-shot trigger circuit OS be output as H level during in charged, as shown in (d) in Figure 31, make to rise gradually to the output voltage of output comparator CP10.Here, it is during the output of single-shot trigger circuit OS is the output H level of H level and output comparator CP10 that the 36d of zero current detection portion in Figure 31 shown in (g) is output as during H level, in Figure 31 the output of the output comparator CP10 shown in (f) during H level is reversed to the pulse duration amount of L level output tight, single-shot trigger circuit OS, thus, the output of the 36c of power drives portion becomes in Figure 31 output such shown in (a).As long as the output of output comparator CP10 is not H level, the output of the 36d of zero current detection portion does not just become H level, so to the input voltage of the 36d of zero current detection portion lower than the 9th reference voltage Vr9 after, in the retention time T6 of the regulation before the both end voltage that retains electricity consumption container C 107 has reached the 10th reference voltage Vr10, the output of the 36d of zero current detection portion does not become H level.In other words, as long as the duration to the input voltage of the 36d of zero current detection portion during lower than the 9th reference voltage Vr9 does not reach above-mentioned retention time T6, the output of flip-flop circuit 36b does not just become H level, thereby the switch element Q4 of DC power supply portion 1 is not switched on.

In addition, in DC power supply portion 1, due to the contrary recovery time of spurious impedance and diode D1, after switch element Q4 has just been switched on, from the electric current (hereinafter referred to as " adverse current electric current ") of output capacitor C6, flows to and detect with in resistance R3.In addition driving with in integrated circuit 3, if declined to the input voltage input supply voltage of the reversion input terminal that is connected to the comparator C P7 on the reseting terminal of flip-flop circuit 36b, decline.And, at input supply voltage, with respect to above-mentioned countercurrent electric rheology output low, above-mentioned comparator C P7, become H level, although do not put aside fully energy in inductor L2, switch element Q4 is also disconnected.In the case, although can, again by switch element Q4 conducting in the very short time, again be disconnected with above-mentioned same switch element Q4, can expect by this repeatedly and switch element Q4 is switched on disconnection with the shorter cycle.If switch element Q4 is switched on disconnection with the shorter cycle like this, the electric stress of overaction on switch element Q4.

With respect to this, in the present embodiment, as mentioned above, as long as the duration to the input voltage of the 36d of zero current detection portion during lower than the 9th reference voltage Vr9 does not reach retention time T6, just not by the switch element Q4 conducting of DC power supply portion 1, the off-state that is switch element Q4 at least continues retention time T6, even so near the situation that the input voltage of the 36d of zero current detection portion fine changes as the right-hand member of Figure 31 also can avoid the switch element Q4 of DC power supply portion 1 because of the such situation of the conducting disconnection lost of life in the cycle compared with short.

And then, in the present embodiment, the output of the 36d of zero current detection portion is connected to arranging on terminal of flip-flop circuit 36b via logic and circuit OR3, driving with in integrated circuit 3, be provided with monitor the output of flip-flop circuit 36b, when the output of flip-flop circuit 36b continue the stipulated time while being above L level via above-mentioned logic and circuit OR3 the 36e of start portion again that terminal input pulse is set to flip-flop circuit 36.

Here, in execution mode 5, when totally having reached time device lifetime, drive division 31 grades are stopped service time, with respect to this, in the present embodiment, even if totally reached the time device lifetime service time, do not carry out stopping of drive division 31 grades yet, when totally having reached time device lifetime, carry out other actions service time.Below explain.

In the control of present embodiment, use in integrated circuit 4, shown in figure 32, be provided with report portion 48, according to accumulative total be whether service time time device lifetime with on switch output, in making during the accumulative total service time by 46 timing of timing portion, (being the service time of discharge lamp ignition device self) was less than time device lifetime, make to be output as L level, more than accumulative total time device lifetime service time by 46 timing of timing portion during in make to be output as H level.Time device lifetime is for example made as 30,000 hours.In addition,, driving with in integrated circuit 3, be provided with the report input part 38 of the output that is transfused to report portion 48.

And, in reporting that input part 38 is during the output H of report portion 48 level, by the switch element Q108 of the 36d of zero current detection portion is maintained to off-state and the output of output comparator CP10 is fixed as to H level, the output using the output of single-shot trigger circuit OS as the 36d of zero current detection portion.Thus, no longer carry out the off-state of switch element Q4 to guarantee the above-mentioned action of retention time T6, thus the possibility that is switched on disconnection with the shorter cycle because of the abnormal switch element Q4 of AC power AC uprise, the lifetime of switch element Q4 thus.

Here, in the case of can not predict that forming which in the source element of discharge lamp ignition device reaches the life-span at first, difficult establishment be used for preventing discharge lamp ignition device to the life-span time the countermeasure of accident.In addition, in accumulative total according to the rules as Embodiment 5, make service time discharge lamp La turns off the light, in multiple discharge lamp ignition devices of installing at the same time, discharge lamp La is turned off the light simultaneously, is not wish to occur for user.With respect to this, in the present embodiment, by above-mentioned action, easily there is the fault of the switch element Q4 of DC power supply portion 1, so the possibility that switch element Q4 more first reaches the life-span than other circuit elements uprises, so easily establish the countermeasure of known use current fuse (not shown) etc.In addition, because switch element Q4 reaches the life-span, the time of fault exists inhomogeneous, even so start the situation of the use of multiple discharge lamp ignition devices simultaneously, do not have the situation that discharge lamp La is turned off the light simultaneously when the life-span of these multiple discharge lamp ignition devices yet.

Action while in addition, totally reaching time device lifetime is not limited to the above service time.For example, also can adopt following structure: clock portion 45 changes according to the output of report portion 48 that not to be transfused to report be the clock frequency in stopping of drive division 31 during voltage vcc 3, after totally having reached the time device lifetime service time, make above-mentioned clock frequency ratio add up service time and reach time device lifetime height before.More particularly, for example accumulative total service time before reaching the time device lifetime clock frequency TA make be not transfused to report power supply cc3 during same with execution mode 4 lower than the clock frequency TB in operating stably, on the other hand, after adding up service time to reach time device lifetime, make not to be transfused to the clock frequency TA reporting during power supply cc3 identical with the clock frequency TB in operating stably.In the case, because the electric stress acting in the stopping of drive division 31 on the 1st switch element Q101 of startup portion 32 becomes large, the 1st switch element Q101 of startup portion 32 reaches at first the possibility in life-span and uprises.If adopt this structure, the output of report portion 48 is only interior processed with integrated circuit 4 in control, so no longer need to be in driving with report input part 38 being set, can realizing thus driving the miniaturization of using integrated circuit 3 in integrated circuit 3.

(execution mode 11)

The basic structure of present embodiment and execution mode 10 are common, so give identical label for common part, omit diagram and explanation.

In the present embodiment, as shown in figure 33, as the structure of oscillating portion 35, adopt structure as shown in Figure 11 in execution mode 3.In addition, in Figure 33, for the circuit that regulates control part 44 and periphery thereof, omitted diagram.

In the present embodiment, report input part 38 is connected to and in report portion 48 and in non-reversion input terminal, is transfused to the 11st reference voltage Vr11 of regulation and lead-out terminal is connected to via resistance R 33 to control and forms by the comparator C 11 on the reversion input terminal of operational amplifier OP2 by reversion input terminal.Make the 11st reference voltage Vr11 lower and higher than the magnitude of voltage of the output of the L level of report portion 48 than the magnitude of voltage of the output of the H level of report portion 48, the output of report input part 38 is the output reversion that the output of above-mentioned comparator C 11 makes report portion 48.In addition, by connection as described above, operating frequency shown in Figure 34 (c) in (being during discharge lamp ignition device is judged as end of lifetime) T9, T10, is made as high frequency f 4, the f5 of operating frequency f1, f2 of (being during discharge lamp ignition device is not judged as end of lifetime) T7, T8 during being output as L level than report portion 48 during the report portion 48 shown in (a) is output as H level in Figure 34.Thus, the amplitude of the output voltage from resonant structure 22 to discharge lamp La shown in Figure 34 (b) T9, T10, is little amplitude V2, the V4 of amplitude V1, V3 in T7, T8 during the output L level than report portion 48 during the output H of report portion 48 level.And then, the sequential control portion 41 of present embodiment is during the output H of report portion 48 level in T9, T10, than T7, T8 during the output L level of report portion 48, make pre-thermally operated duration T 7, T9 length and make to start the duration T 8, the T10 that move short.

According to said structure, in during discharge lamp ignition device is judged as end of lifetime, by making the pre-thermally operated duration elongated, the life-span of discharge lamp La easily shortens, and by operating frequency is uprised, the startability variation of discharge lamp La, so user likely knows the end of lifetime of discharge lamp ignition device.As the pre-thermally operated duration T 9 during the output H level of report portion 48, particularly for example be made as 2 times～3 times of pre-thermally operated duration T 7 during the output L level of report portion 48, can make thus the pre-thermally operated duration excessive and make the lifetime of discharge lamp La reliably.And then if made, pre-thermally operated duration T 9 during the output H level of report portion 48 is elongated sees the degree of just knowing to people, more easily knows the end of lifetime of discharge lamp ignition device for user.

(execution mode 12)

The basic structure of present embodiment and execution mode 11 are common, so give identical label for common part, omit diagram and explanation.

In the driving of present embodiment, use in integrated circuit 3; as shown in figure 35, replace the low judging part 37 of direct voltage and being provided with to judge whether being the output voltage V dc of DC power supply portion 1 to become abnormal high overvoltage condition and when be judged as overvoltage condition, make the overvoltage protection portion 39 of the output voltage decline of DC power supply portion 1.In addition, report input part 38 is connected in overvoltage protection portion 39, and overvoltage protection portion 39 changes action according to the output of report portion 48.

Overvoltage protection portion 39 as shown in figure 36, possess in non-reversion input terminal, be transfused to the output of DC power supply test section 167 and reversion be transfused in input terminal regulation the 12nd reference voltage Vr12 comparator 12 and the output of this comparator C P12 and the logic product of the output of report input part 38 are outputed to the logic integrated circuit AND3 in the reseting terminal of flip-flop circuit 36b.; when totally not reaching the time device lifetime service time; when exceeding the 12nd reference voltage Vr12, the output voltage of DC power supply test section 167 carries out disconnecting and controlling the overvoltage protection action that the output voltage V dc of DC power supply portion 1 is declined by the switch element Q4 to DC power supply portion 1; when accumulative total reaches after the time device lifetime service time; because the output of report input part 38 becomes L level; the output of logic integrated circuit AND3 is fixed to L level, no longer carries out above-mentioned overvoltage protection action.

According to said structure, in accumulative total, reached after the time device lifetime service time, because no longer carry out overvoltage protection action, the easily higher electric stress of effect on the switch element Q4 of DC power supply portion 1, so can obtain the effect same with execution mode 10.; the possibility that more first reaches the life-span than other circuit elements due to switch element Q4 uprises; so easily establish the countermeasure of known use current fuse (not shown) etc.; in addition; because switch element Q4 reaches the life-span, the timing of fault exists inhomogeneous; even so start the situation of the use of multiple discharge lamp ignition devices simultaneously, do not have the situation that discharge lamp La is turned off the light simultaneously when the life-span of these multiple discharge lamp ignition devices yet.

In addition; overvoltage protection portion 39 is not limited to the above; also can logic integrated circuit AND3 be set and for example be configured to like that as shown in figure 37; the 13rd reference voltage Vr13 of the 12nd reference voltage Vr12 and the high regulation of Bi 12 reference voltage Vr12 is input in comparator C P12 via the multiplexer TG3 that uses transmission gate circuit to form respectively, the voltage being input in the reversion input terminal of comparator C P12 of overvoltage protection portion 39 is made as to the 13rd reference voltage Vr13 higher than the 12nd reference voltage Vr12 in during the output H of report portion 48 level.If adopt this structure, the voltage being input to after reaching the time device lifetime service time in the reversion input terminal of comparator C P12 of overvoltage protection portion 39 in accumulative total uprises, and is difficult for carrying out overvoltage protection action, can obtain thus same effect.

Here, in above-mentioned various discharge lamp ignition devices, rectification part DB, DC power supply portion 1, switch portion 21, resonant structure 22, driving are for example arranged on respectively on OBL printed wiring board 70 as shown in Figure 38 with integrated circuit 3 and control integrated circuit 4.In the example of Figure 38, on one end of the length direction of printed wiring board 70, be provided with and connecting the power supply connector CN3 that connects the electric wire of use to AC power AC, on the other end of the length direction of printed wiring board 70, be provided with a pair of load use connector CN1, the CN2 that are electrically connected to lamp socket 81 electric with discharge lamp La and that be mechanically connected (with reference to Figure 41).In addition, from above-mentioned one end of printed wiring board 70 towards the above-mentioned other end, with rectification part DB, DC power supply portion 1, drive with integrated circuit 3, control the arranged in order with integrated circuit 4 and switch portion 21, resonant structure 22, switch portion 21 and controlling by integrated circuit 4 alignment arrangements on the short side direction of printed wiring board 70.In addition, the output capacitor C6 of DC power supply portion 1 is arranged on to have installed and drives with integrated circuit 3 and control on the opposing face of the face of using integrated circuit 4 on printed wiring board 70.

And then, in the example of Figure 38, the ground connection figure 71 that is located at current potential in the conductive pattern 71,72 on printed wiring board 70, that be made as ground connection is observed from the thickness direction of printed wiring board 70, is configured in to drive with integrated circuit 3 and control integrated circuit 4, and be connected between the high-pressure side figure 72 and switch portion 21 on the output of high-voltage side of DC power supply portion 1.In addition, in ground connection figure 71, connecting to drive and be branched to than the thin position, position that is connecting respectively DC power supply portion 1, switch portion 21 and resonant structure 22 with the position of integrated circuit 4 with integrated circuit 3 and control, on this thin position, be respectively equipped with from the thickness direction of printed wiring board 70 and observe a difference part and drive two loop 71a, the 71bs overlapping with one of integrated circuit 3 and control integrated circuit 4.Thus, drive with integrated circuit 3 and control by the situation between integrated circuit 4 and switch portion 21 or do not make the situation of ground connection figure 71 branches or do not arrange compared with the situation of loop 71a, 71b with ground connection figure 71 not being observed to be configured in from the thickness direction of printed wiring board 70 as shown in Figure 39, can reduce the impact that the radiated noise that switch portion 21 produces and the conducted noise of propagating bring with integrated circuit 4 to driving integrated circuit 3 and control and improve noise tolerance in ground connection figure 71.In addition,, for the inhibition of common-mode noise, preferred above-mentioned ground connection figure 71 is via capacitive impedance ground connection.

Printed wiring board 70 as described above is accommodated in housing 73 such shown in Figure 40 (a)～Figure 40 (c).Here, the input of the signal shown in Figure 40 (a) connection for the such outside sensor of the lightness transducer 63 of execution mode 3 with connector CN4.

And then above-mentioned housing 73 is received and is remained in the appliance body 80 shown in Figure 41 and forms ligthing paraphernalia 8.The appliance body 80 of Figure 41 is mounted in the ligthing paraphernalia 8 of the so-called Fuji type using on ceiling, is triangular prism shape on the whole, is keeping respectively the lamp socket 81 of the connection use of discharge lamp La on the both ends of length direction.In addition, make the outer surface of appliance body 80 for for example white, with the light luminous intensity distribution to discharge lamp La.In addition, in the case of arranging (or be preferably the expose) transducer that need to expose, as long as like that suitably arrange as shown in figure 42, be used for making that transducer exposes that to expose hole 80a just passable as the lightness transducer 63 of execution mode 3.

(execution mode 13)

Below, utilize accompanying drawing to describing about the supply unit of embodiments of the present invention 3.In addition, in the present embodiment, as described later, load circuit 302 is configured to by the converter portion 320 that is high frequency voltage by the DC voltage conversion from DC power supply circuit 301 and is applied in from the high frequency voltage of converter portion 320 and by resonance effect resonant structure 321 that discharge lamp La lights a lamp etc. is formed, be used for discharge lamp La to supply with the electric power of lighting a lamp, but load circuit 302 is not limited to this structure, also can be the structure of the load (for example, as long as lighting source is just passable, light-emitting diode etc.) beyond discharge lamp La being supplied with to action electric power.

Present embodiment as shown in figure 43, by by the ac voltage rectifier from AC power AC and the rectification circuit DB being formed by diode bridge of output ripple voltage, in the future the pulsating voltage of self-rectifying circuit DB boosts and smoothing and the DC power supply circuit 301 of output dc voltage, by the DC voltage conversion from DC power supply circuit 301, be high frequency voltage and high frequency voltage is applied to the upper load circuit 302 that discharge lamp La is lit a lamp of discharge lamp La, the converter control circuit 306 of the converter described later portion 320 that controls the DC power control circuit 305 of DC power supply circuit 301 and control load circuit 302 is formed in to the control circuit 303 forming on same semiconductor substrate, and be used for the action initialization circuit 304 of action of setup control circuit 303 and form.

DC power supply circuit 301 is the boost choppers that consist of inductor L301, switch element Q301, diode D301, smoothing capacitor C301, thereby by boosting according to the pulsating voltage of the ON/OFF self-rectifying circuit DB in future that carrys out diverter switch element Q301 from the driving signal of DC power control circuit 305 described later, the direct voltage that the pulsating voltage boosting has been carried out to smoothing is supplied in load circuit 302.In addition, at the input side of DC power supply circuit 301, be provided with the input voltage test section 310 of the input voltage for detecting DC power supply circuit 301, at outlet side, be provided with the output voltage test section 311 of the output voltage for detecting DC power supply circuit 301.In addition, switch element Q301 consists of MOSFET, and its gate terminal is connected on the 301st drive division 350 described later via resistance R 301.In addition, connecting resistance R 302 on the source terminal of switch element Q301, the falling quantity of voltages of resistance R 302 is input in the non-reversion input terminal of the 2nd operational amplifier OP302 described later via the filter portion 355 consisting of resistance R 305 and capacitor C307.By this filter portion 355, the impact switch element Q301 of the peak current while preventing from switching to conducting because of switch element Q301 switches to disconnection.In addition, input voltage test section 310 and output voltage test section 311 all form (input voltage test section 310 is with reference to Figure 47, and output voltage test section 311 is with reference to Figure 56) by resistance and capacitor, are known, so omit detailed explanation here.

Load circuit 302 consists of following part: converter portion 320, there is 1 couple of switch element Q302, Q303 being connected in series, by according to the ON/OFF of alternately switching these switch elements Q302, Q303 from the driving signal of converter control circuit 306 described later, by the DC voltage conversion from DC power supply circuit 301, be high frequency voltage; Resonant structure 321, consists of capacitor C302, C303 and inductor L302, is applied in the high frequency voltage from converter portion 320, by resonance effect, discharge lamp La is lit a lamp; Preheating part 322, consists of capacitor C304, C305, C306 and transformer T301, is applied in from the high frequency voltage of converter portion 320 and by discharge lamp La preheating; And control power supply generative circuit 323, and be applied in the high frequency voltage from converter portion 320, generate the described later the 2nd and control power Vcc 302.In addition, switch element Q302, Q303 consist of MOSFET, between the gate terminal of each switch element Q302, Q303 and the 2nd drive division 360 described later, are inserted with respectively resistance R 303, R304.

Control circuit 303 starts the startup portion 330 of the 2nd control power Vcc 302 by accepting the output voltage of DC power supply circuit 301, by the control power supply comparing section 331 of the 2nd control supply voltage of power Vcc 302 and the supply voltage comparison of the 3rd reference voltage source Vref303 described later, according to the comparative result of controlling power supply comparing section 331, generate the 1st of the 1st control power Vcc 301 and control power supply generating unit 332, according to generating the 3rd of the 3rd control power Vcc 303 from the output signal that stops enforcement division 334 described later, control power supply generating unit 333, and form according to the enforcement division 334 that stops that stopping judged result control the 1st drive division 350 of judging part 342 and the action of the 2nd drive division 360 described later.

Action initialization circuit 304 is by the sequential control portion 340 that consists of to carry out frequency setting described later portion 341 microcomputer and stop the sequential control of judging part 342, output is used for setting the switch element Q302 of converter portion 320, the frequency setting portion 341 of the frequency setting signal of the driving frequency of Q303, what according to the sequential control output of sequential control portion 340, make stop signal that the action of the 1st drive division 350 and the 2nd drive division 360 stops stops judging part 342, and the cycle configuration part 343 of setting the clock cycle of action initialization circuit 304 forms.

The 1st drive division 350 of the driving signal that the ON/OFF of DC power control circuit 305 switch element Q301 to DC power supply circuit 301 by output is switched, if flow through the electric current of inductor L301 via the secondary coiling of the inductor L301 of DC power supply circuit 301, become the current value of regulation with the zero current detection portion 351 of next output zero-signal, control the rest-set flip-flop 352 of the action of the 1st drive division 350, by the 1st operational amplifier OP301 of the supply voltage comparison of the detection voltage of output voltage test section 311 and the 1st reference voltage source Vref301, the multiplier 353 that the output voltage of the detection voltage of input voltage test section 310 and the 1st operational amplifier OP301 is multiplied each other, and the 2nd operational amplifier OP302 of the output voltage comparison of the falling quantity of voltages in the resistance R of DC power supply circuit 301 302 and multiplier 353 is formed.In addition, if more than forming the electric current flowing through become the current value of regulation in switch element Q301 by the 1st operational amplifier OP301, the 2nd operational amplifier OP302 and multiplier 353, the peak current detection portion that exports peak signal.

Converter control circuit 306 is by by the 2nd drive division 360 of the driving signal output of the ON/OFF of switch element Q302, the Q303 of switching converter portion 320 alternately and make to drive the changeable frequency portion 361 of the variable frequency of signal to form according to the frequency setting signal of exporting from the frequency setting portion 341 of action initialization circuit 304.

Below, the action of present embodiment is described.First, utilize Figure 44, Figure 45 to describe the action of control circuit 303.If connect the power supply of present embodiment, the output voltage of DC power supply circuit 301 is imported in the load circuit 302 of rear class and the startup portion 330 of control circuit 303.Power supply rigidly connect logical after, the output voltage of DC power supply circuit 301 is by the smooth voltage of the alternating voltage of AC power AC smoothing capacitor C301 smoothing, by this smooth voltage via the withstand voltage resistance R 306 of height by electric current supply in the series circuit of diode D302 and Zener diode ZD301.By the voltage VG producing between the two ends of this series circuit is input in the gate terminal of the switch element Q304 consisting of the withstand voltage MOSFET of height, switch element Q304 switches to conducting, and the 2nd controls power Vcc 302 starts.And the 2nd controls the supply voltage of power Vcc 302 and detection voltage Va described later, Vb, Vc rise in time (with reference to Figure 45 (a), Figure 45 (b)).

By the 2nd supply voltage of controlling power Vcc 302, by the series circuit dividing potential drop being formed by resistance R 307～R310, be to detect voltage Va, Vb, Vc (Va > Vb > Vc).By detecting voltage Va, be input in the non-reversion input terminal of the 4th operational amplifier OP304 that controls power supply comparing section 331, with the supply voltage comparison that is input to the 3rd reference voltage source Vref303 in reversion input terminal.By detecting voltage Vb, Vc via the 1st multiplexer circuit MP301 with the 1 pair of transmission gate element that is transfused to each voltage, be input in the non-reversion input terminal of the 3rd operational amplifier OP303.The output signal of the 3rd operational amplifier OP303 and the output signal that stops enforcement division 334 described later are input in OR element OR301 to the ON/OFF of the switch element Q305 being formed by MOSFET being connected in parallel by the output signal control of OR element OR301 and the series circuit of diode D302 and Zener diode ZD301.In addition, power supply rigidly connect logical after, the output signal that stops enforcement division 334 is L (low) level, so the ON/OFF of the output signal control switch element Q305 by the 3rd operational amplifier OP303 only.

At the beginning of the 2nd control power Vcc 302 starts, by the 1st multiplexer circuit MP301, by detecting voltage Vc, be input in the non-reversion input terminal of the 3rd operational amplifier OP303, with the supply voltage comparison that is input to the 2nd reference voltage source Vref302 in reversion input terminal.And, if detection voltage Vc reaches the supply voltage of the 2nd reference voltage source Vref302, the output signal of the 3rd operational amplifier OP303 reversion, detects voltage Vb by the 1st multiplexer circuit MP301 to the non-reversion input terminal input of the 3rd operational amplifier OP303.Simultaneously, by the output signal of the 3rd operational amplifier OP303 is input in the gate terminal of switch element Q305 via OR element OR301, switch element Q305 switches to conducting, and switch element Q304 switches to disconnection (with reference to Figure 45 (b), Figure 45 (c)).

Switch element Q304 switches to disconnection, the 2nd controls the supply voltage of power Vcc 302 and detects voltage Va, Vb, Vc decline thus.And, if detection voltage Vb reaches the supply voltage of the 2nd reference voltage source Vref302, the output signal of the 3rd operational amplifier OP303 reversion, is input in the non-reversion input terminal of the 3rd operational amplifier OP303 detecting voltage Vc again by the 1st multiplexer circuit MP301.In addition,, along with the reversion of the output signal of the 3rd operational amplifier OP303, switch element Q305 switches to and disconnects and switch element Q304 switches to conducting.Thereby the supply voltage of the 2nd control power Vcc 302 and detection voltage Va, Vb, Vc transfer rising again to.By repeatedly carrying out above-mentioned action, the grid voltage of switch element Q304 becomes shown in Figure 45 (c) ON/OFF like that repeatedly.

In addition, the 2nd supply voltage of controlling power Vcc 302 is imported in the collector terminal of the switch element Q307 consisting of bipolar transistor of the 1st control power supply generating unit 332.The 1st controls the Zener diode ZD302 that power supply generating unit 332 is connected in series by the 1st constant current source Iref301 between switch element Q307, the collector terminal that is connected to switch element Q307 and base terminal, with the 1st constant current source Iref301 and forms with the switch element Q306 consisting of MOSFET that Zener diode ZD302 is connected in parallel.In the gate terminal of switch element Q306, be transfused to the output signal of the 4th operational amplifier OP304 that controls power supply comparing section 331.So, the 2nd supply voltage of controlling power Vcc 302 rises, if detect the supply voltage that voltage Va exceedes the 3rd reference voltage source Vref303, switch element Q307 switches to conducting, the 1st control power Vcc 301 rises, by power supply voltage supplying to action initialization circuit 304 in (with reference to Figure 45 (b), Figure 45 (d)).In addition, the supply voltage of the 3rd reference voltage source Vref303 equates with the supply voltage of the 2nd reference voltage source Vref302.

If controlling power Vcc 301 from the 1st rises through T1 specified time limit, from stopping enforcement division 334, export H (height) level signal (with reference to Figure 45 (e)), accept this H level signal and generate the 3rd in the 3rd controls power supply generating unit 333 to control power Vcc 303 (with reference to Figure 45 (g)).In addition, by supplying with the supply voltage of the 3rd control power Vcc 303, the action of the 1st drive division 350 of DC power control circuit 305 starts (with reference to Figure 45 (f)).In addition, the 3rd supply voltage of controlling power Vcc 303 is also supplied in converter control circuit 306, with the timing identical with the 1st drive division 350, starts action.So the converter portion 320 of load circuit 302 starts action.In addition, about the details of action initialization circuit 304, narrate in the back.

Converter portion 320 starts action, from controlling power supply generative circuit 323, control circuit 303 is supplied with thus the supply voltage of the 2nd control power Vcc 302.Therefore, detect the supply voltage that voltage Vb, Vc always exceed the 2nd reference voltage source Vref302, switch element Q304 maintains the state (with reference to Figure 45 (b), Figure 45 (c)) of disconnection.In addition, in the present embodiment, in order to maintain reliably the off-state of switch element Q304, by output signal and the output signal that stops enforcement division 334 of the 3rd operational amplifier OP303, carry out the ON/OFF of control switch element Q304.; owing to stopping the output signal of enforcement division 334 when the action of converter portion 320, it is always H level; even so the 2nd supply voltage output signal low and the 3rd operational amplifier OP303 of controlling power Vcc 302 is reversed, also can maintain the off-state of switch element Q304.

In addition, in the case of the action of converter portion 320 stops, low from the service voltage of controlling power supply generative circuit 323, detect thus the supply voltage of voltage Vb lower than the 2nd reference voltage source Vref302, switch element Q304 carries out ON/OFF action (with reference to Figure 45 (b), Figure 45 (c)) again repeatedly.This ON/OFF action is as long as the smooth voltage of exporting from DC power supply circuit 301 is that enough sizes are just proceeded.

In addition, control power supply generative circuit 323 as long as generating according to the switch motion of converter portion 320 structure of the 2nd control power Vcc 302, be what kind of structure can, as long as supply voltage more than 10V to can drive each switch element Q301～Q303 just passable.

Then, utilize accompanying drawing to describe changeable frequency portion 361.Changeable frequency portion 361 as shown in figure 46, by the constant-voltage circuit forming by the 5th operational amplifier OP305, be connected on the lead-out terminal of the 5th operational amplifier OP305 by resistance R 311, the load impedance circuit that R312 forms, there is the 6th operational amplifier OP306 of the supply voltage that is transfused to the 4th reference voltage source Vref304 in non-reversion input terminal, according to the current mirroring circuit CM that flows to electric current in load impedance circuit and regulate the electric current that flows through capacitor C309, by thering is the 2nd multiplexer circuit MP302 of a pair of transmission gate element being connected with the 5th reference voltage source Vref305 and the 6th reference voltage source Vref306 respectively and by the oscillating circuit that between the 2nd output voltage of multiplexer circuit MP302 and the two ends of capacitor C309, voltage ratio the 7th operational amplifier OP307 forms, and generation is used for preventing the switch element Q302 of converter portion 320, generating unit 361a dead time of the dead time of Q303 conducting simultaneously forms.

In the non-reversion input terminal of the 5th operational amplifier OP305, via the filter circuit being formed by resistance R 313, R314, R315 and capacitor C308, be transfused to the frequency setting signal of exporting from the frequency setting portion 341 of action initialization circuit 304.Frequency setting signal is for example the square-wave signal of duty ratio with regulation such shown in Figure 47 (d), is transformed to the direct current signal corresponding to duty ratio in filter circuit.Here, because the lead-out terminal of the 5th operational amplifier OP305 is connected to via resistance 4311 on the lead-out terminal of the 6th operational amplifier OP306, so by changing the duty ratio of frequency setting signal, flow to the size variation of the electric current the lead-out terminal of the 6th operational amplifier OP306 from the lead-out terminal of the 5th operational amplifier OP305.So, by changing the duty ratio of frequency setting signal, can changing, flow through the electric current of capacitor C309 and change the driving frequency that drives signal.

In addition, drive signal via dead time generating unit 361a be imported into respectively in the high side drive 360a of portion and the 360b of low side drive portion of the 2nd drive division 360, by the ON/OFF of each drive division 360a, 360b control switch element Q302, Q303.

Then, utilize Figure 43 to describe DC power control circuit 305.DC power control circuit 305 carries out by the ON/OFF of diverter switch element Q301 repeatedly to the savings of the energy of inductor L301 and from the release of the energy of inductor L301, and switch element Q301 carries out to switching in from the timing of the release of the energy of inductor L301 of conducting.Therefore, in DC power control circuit 305, be provided with as shown in figure 43 zero current detection portion 351, in zero current detection portion 351, secondary coiling voltage drop by detecting inductor L301 is near timing 0V, judges from the timing below the current value that inductor L301 has discharged the timing of energy, the electric current that flows through inductor L301 becomes regulation.In zero current detection portion 351, if judge from inductor L301 and discharged energy, to rest-set flip-flop 352 terminal input H level signal is set, via the 1st drive division 350, make switch element Q301 switch to conducting.In addition, about the details of zero current detection portion 351, narrate in the back.

In addition, the in the situation that of switch element Q301 conducting, by resistance R 302, detect the electric current that flows through switch element Q301, the output voltage of the falling quantity of voltages in resistance R 302 and multiplier 353 is compared in the 2nd operational amplifier OP302.And, if the electric current that the falling quantity of voltages in resistance R 302 exceedes the output voltage of multiplier 353, flow through switch element Q301 exceedes setting, the reseting terminal input H level signal (peak signal) to rest-set flip-flop 352, makes switch element Q301 switch to disconnection via the 1st drive division 350.In addition, afore mentioned rules value be supply voltage by the output voltage of DC power supply circuit 301 being detected to 311 detection voltage and reference voltage source Vref301 in the 1st operational amplifier OP1 relatively and carry out FEEDBACK CONTROL and determine.

Below, utilize the time diagram shown in Figure 47 to describe the sequential control of present embodiment.By the filament of preheating discharge lamp La in advance between warming up period, for discharge lamp La is started, utilize resonance effect to discharge lamp La apply between the high-tension starting period, make that discharge lamp La lights a lamp with the light output of hope light a lamp during each during the processing of sequential control as in the past, carried out, utilize in the present embodiment action initialization circuit 304 to carry out said sequence control.

As shown in Figure 47 (a), if the 1st controls that power Vcc 301 rises and to action initialization circuit 304 supply line voltages, to the input signal that stops enforcement division 334, the 1st, controlling moment that power Vcc 301 rises becomes L level (with reference to Figure 47 (b)) after becoming H level.And, the specified time limit before the output signal that stops enforcement division 334 becomes H level during T1 in, the action of changeable frequency portion 361, the 1st drive division 350, the 2nd drive division 360 stops.

Here, if form the microcomputer of action initialization circuit 304, from the 1st, controlled power Vcc 301 supply line voltages, predefined initial start-up routine action, carries out the function of microcomputer terminal and distributes, but now have the impedance of terminal to become infinitely-great situation.So, in the present embodiment, the 1st, control power Vcc 301 and stop contact resistance R316 between the lead-out terminal of judging part 42, prevent that the output of microcomputer terminal from becoming unstable.

If through T1 during afore mentioned rules, as shown in Figure 47 (c), the stop signal of carrying out self-stopping technology enforcement division 334 becomes H level, the action of changeable frequency portion 361, the 1st drive division 350, the 2nd drive division 360 starts, and converter portion 320 moves with the driving frequency of being set by frequency setting portion 341.Here, the frequency setting signal of exporting from frequency setting portion 341, as shown in Figure 47 (d), changes respectively duty ratio during from the moment t1 of the action that starts converter portion 320 to the lighting a lamp the starting period warming up period, from moment t2 to moment t3, after moment t3 in advance of moment t2.Therefore, the output signal of the 5th operational amplifier OP305 changes as shown in Figure 47 (e) along with the variation of the duty ratio of frequency setting signal.Thereby, driving frequency in advance between warming up period for frequency f 1, between the starting period in for frequency f 2, lighting a lamp during in change successively (with reference to Figure 47 (f)) for frequency f 3.So, discharge lamp La through in advance between warming up period, between the starting period and light a lamp.

Here, the time constant of the filter circuit consisting of resistance R 313, R314, R315 and capacitor C308 of input prime that is located at the 5th operational amplifier OP305 is made as to the output voltage that makes filter circuit stable in during specified time limit T1, the output voltage stabilization (with reference to Figure 47 (e)) of the 5th operational amplifier OP305 while starting between warming up period in advance thus, therefore can make driving frequency stabilisation.

In addition, in advance between warming up period and between the starting period as long as determined just passablely by action initialization circuit 304, generally need only by being assembled in built-in oscillator or timer circuit timing in microcomputer just passable.In addition, in the present embodiment, the clock cycle based on being set by cycle configuration part 343 described later is decided the routine processes speed of microcomputer.

In addition, the duty ratio of the frequency setting signal of exporting from frequency setting portion 341 is 0% in advance between warming up period, in between the starting period after the having stable behavior of converter portion 320, just start to improve duty ratio, so can reduce the action of converter portion 320, just started the current sinking in control circuit 303 afterwards and action initialization circuit 304, made the supply stabilisation from the supply voltage of each control power supply.And then, by when the action that makes converter portion 320 stops in the future the stop signal of self-stopping technology judging part 342 be made as H level (being soon made as H level to the input signal that stops enforcement division 334), can make electric current not flow in resistance R 316, the current sinking in the control circuit 300 when the action that can reduce converter portion 320 stops.In addition, by not using A/D translation circuit and D/A translation circuit to use the diadic of H level/L level to process the input/output signal of the microcomputer that forms action initialization circuit 304, can significantly reduce the current sinking in microcomputer.In the case, the stress of the switch element Q304 to startup portion 330 also significantly reduces, so can make 330 miniaturizations of startup portion.

Then, utilize accompanying drawing to describe stopping enforcement division 334.Stop enforcement division 334 as shown in figure 48, by be transfused to the detection voltage of input voltage test section 310 and come the stop signal voltage of self-stopping technology judging part 342 stop signal input part 334a, accept from the output signal of stop signal input part 334a and the dwell time timing 334b of portion that makes the time timing that the action of changeable frequency portion 361, the 1st drive division 350, the 2nd drive division 360 stops formed.

Stop signal input part 334a is by being transfused to the supply voltage of the 7th reference voltage source Vref307 and being transfused to the 8th operational amplifier OP308 of the detection voltage of input voltage test section 310 in input terminal in reversion in non-reversion input terminal, in non-reversion input terminal, be transfused to the 9th operational amplifier OP309 that carrys out the stop signal voltage of self-stopping technology judging part 342 and be transfused to the supply voltage of the 7th reference voltage source Vref307 in reversion input terminal, and be transfused to each operational amplifier OP308, the OR element OR302 of the output signal of OP309 forms.

The dwell time timing 334b of portion is by the switch element Q308 that consists of MOSFET and be transfused in gate terminal from the output signal of stop signal input part 334a, be connected to the capacitor C310 on the drain terminal of switch element Q308, capacitor C310 is supplied with to the 2nd constant current source Iref302 of electric current, the 10th operational amplifier OP310 that is transfused to voltage between the two ends of capacitor C310 and is transfused to the supply voltage of the 8th reference voltage source Vref308 in non-reversion input terminal in reversion input terminal forms.Switch element Q308 is according to the output signal switched conductive/disconnection from stop signal input part 334a, in the situation that switch element Q308 disconnects, the charging interval determining with the static capacity of the electric current by flowing out from the 2nd constant current source Iref302 and capacitor C310 is charged capacitor C310.

Here, if the detection voltage of the 8th operational amplifier OP308 input voltage test section 310 exceedes assigned voltage (supply voltage of the 8th reference voltage source Vref308), export H level signal.On the other hand, the 9th operational amplifier OP309 is L level, to export L level signal in the case of carrying out the stop signal of self-stopping technology judging part 342, is to export H level signal in the situation of H level.Thereby, at the detection voltage of input voltage test section 310, be only below assigned voltage and the stop signal of carrying out self-stopping technology judging part 342 is L level, switch element Q308 switches to and disconnects and capacitor C310 is charged.And, if the charging voltage of capacitor C310 exceedes assigned voltage (supply voltage of the 8th reference voltage source Vref308), from the 10th operational amplifier OP310 output H level signal, in the 3rd controls power supply generating unit 333, generate the 3rd as described above and control power Vcc 303, the action of changeable frequency portion 361, the 1st drive division 350, the 2nd drive division 360 starts.That is, the charging interval of above-mentioned capacitor C310 is T1 during afore mentioned rules, and in this period, the action of converter portion 320 stops.

Below, utilize the elemental motion of the flowchart text action initialization circuit 304 shown in Figure 49.First, if from the 1st control power Vcc 301 supply line voltages (connect the 1st and control power Vcc 301), (S301), initial start-up routine action, carry out initial setting (S302), cycle configuration part 343 starts action (S303).The clock signal being generated by this cycle configuration part 343 is used as the fundamental clock of the microcomputer that forms action initialization circuit 304, suitably switched in the present embodiment two clock signals coming life cycle TA, TB (TA > TB).The cycle of clock signal is shorter, and the current sinking in microcomputer more increases, so the clock signal of life cycle TA first here.

Then,, by the Information Read-Out of the duty ratio of pre-stored frequency setting signal (S304), set the frequency setting signal (S305) of output.Then, start timing (S306), the judgement (S307) during the time based on timing moves.; if reach moment t1, be judged as in advance between warming up period; and setpoint frequency setting signal is so that driving frequency becomes frequency f 1 (S309); if reach moment t2, be judged as between the starting period; and setpoint frequency setting signal is so that driving frequency becomes frequency f 2 (S310); if reach moment t3, during being judged as and lighting a lamp, and setpoint frequency setting signal is so that driving frequency becomes frequency f 3 (S312).In addition, from starting action initialization circuit 304 till the specified time limit of moment t1 during T1, the action of converter portion 320 is stopped (S308).

In addition, in the present embodiment, although not diagram, but be separately provided with the abnormal known abnormal detection circuit in the past whether detection has normally been installed discharge lamp La and whether reached life-span of discharge lamp La etc., in above-mentioned action, in abnormal detection circuit, detect abnormal in the situation that the action of control circuit 303 is stopped.In the case of carrying out like this life tests of discharge lamp La, life tests is moved immediately in especially need to be during the lighting a lamp of discharge lamp La.

So, transfer to light a lamp during time, switched to period T B (S311) in cycle configuration part 343 cycle of clock signal.By like this cycle of clock signal being switched to the period T B shorter than period T A, even if make the thirty years of age life tests action that accelerates of the processing speed of microcomputer.In addition, in the time of during the timing of switching this cycle is not limited to transfer to as described above and lights a lamp, also during during can lighting a lamp from starting between warming up period in advance till transferring to, the supply voltage of from controlling power supply generative circuit 323, control circuit 303 stably being supplied with the 2nd control power Vcc 302 as long as start the action of converter portion 320 is that what kind of timing can.

In addition, detect as described above abnormal and when the action of control circuit 303 is stopped, in the case of in the cycle of clock signal, be period T B, by the cycle of clock signal being switched to period T A in cycle configuration part 343, reduce the current sinking in action initialization circuit 304.So, can reduce to act on the stress in startup portion 330, when restarting, the action that makes converter portion 320 can make the supply stabilisation from the supply voltage of each control power supply.

Then, utilize accompanying drawing to describe zero current detection portion 351.Zero current detection portion 351 as shown in figure 50, by making the shielding part 351a stopping from the output of the zero-signal of zero current detection portion 351 in being transfused to the secondary coiling voltage of inductor L301 in reversion in input terminal and being transfused between the 11st operational amplifier OP311 of the supply voltage of the 9th reference voltage source Vref309, specified time limit after the savings energy of inductor L301 discharges and accept the output signal of the 11st operational amplifier OP311 and only produce 1 ono shot pulse generating unit 351b with the pulse of any amplitude and form in non-reversion input terminal.In addition, arranging between terminal of zero current detection portion 351 and rest-set flip-flop 352, be provided with OR element OR303, in an input terminal of this OR element OR303, be transfused to the output signal of zero current detection portion 351.In addition in another input terminal of OR element OR303, be transfused to again, the output signal of start portion 354.

The opening time timing of start portion 354 to switch element Q301 again, for example, and if (approximately 100 μ s) to exceed specified time limit this opening time, by OR element OR303 is inputted to H level signal, the terminal that arranges to rest-set flip-flop 352 is inputted H level signal, via the 1st drive division 350, switch element Q301 is switched to conducting.In addition, ono shot pulse generating unit 351b and again start portion 354 are in the past known, so omit detailed explanation here.

Shielding part 351a is by being transfused to the output signal of the 11st operational amplifier OP311 and the AND element AND301 via the output signal of the ono shot pulse generating unit 351b of NOT element NOT301, in gate terminal, be transfused to the switch element Q309 being formed by MOSFET of the output signal of AND element AND301, be connected to the capacitor C311 on the drain terminal of switch element Q309, capacitor C311 is supplied with to the 3rd constant current source Iref303 of electric current, in non-reversion input terminal, be transfused to voltage between the two ends of capacitor C311 and in reversion input terminal, be transfused to the 12nd operational amplifier OP312 of the supply voltage of the 10th reference voltage source Vref310, and the AND element AND302 that is transfused to the output signal of the 12nd operational amplifier OP312 and the output signal of ono shot pulse generating unit 351b forms.

Below, utilize Figure 51 to describe the action of zero current detection portion 351.First, under the state disconnecting at switch element Q301, if if the savings energy of inductor L301 discharges, the secondary coiling voltage of inductor L301 is lower than the supply voltage of the 9th reference voltage source Vref309, from the 11st operational amplifier OP311 output H level signal, and from ono shot pulse generating unit 351b output ono shot pulse (with reference to Figure 51 (c), Figure 51 (d), Figure 51 (f)).

Conventionally, in the off period of switch element Q301, because switch element Q309 is off-state, so capacitor C311 is charged by the 3rd constant current source Iref303, because charging voltage has exceeded the 10th reference voltage source Vref310, so from the 12nd operational amplifier OP312 output H level signal.So, by the output signal of the 12nd operational amplifier OP312 and the ono shot pulse of ono shot pulse generating unit 351b, the output signal of AND element AND1 becomes H level, rest-set flip-flop 352 terminal is set in be transfused to H level signal, via the 1st drive division 350, make switch element Q301 switch to conducting (with reference to Figure 51 (a)).In addition, after the ono shot pulse from ono shot pulse generating unit 351b produces, switch element Q309 switches to conducting, so capacitor C311 electric discharge (with reference to Figure 51 (e)).

If switch element Q301 switches to conducting, the electric current that flows through switch element Q301 increases and rises to the input voltage of the 2nd operational amplifier OP302.And, if this input voltage exceedes setting (output voltage of multiplier 353), in the reseting terminal of rest-set flip-flop 352, input H level signal, via the 1st drive division 350, make switch element Q301 switch to disconnection (with reference to Figure 51 (a), Figure 51 (b)).If switch element Q301 switches to disconnection, the secondary of inductor L301 coiling voltage transfers rising (with reference to Figure 51 (c)) to.And, if secondary coiling voltage exceedes the supply voltage of the 9th reference voltage source Vref309, from the 11st operational amplifier OP311 output L level signal, switch element Q309 switches to disconnection, starts the charging (with reference to Figure 51 (d), Figure 51 (e)) of capacitor C311.

The charging voltage of this capacitor C311 needs T2 specified time limit till reaching the supply voltage of the 10th reference voltage source Vref310, during this specified time limit T2 in not from the 12nd operational amplifier OP312 output H level signal.Thereby, in during specified time limit T2, the output signal of AND element AND2 is always L level, so the output signal of the 11st operational amplifier OP311 is H level in this period, even produce ono shot pulse from ono shot pulse generating unit 351b, also the terminal that arranges of rest-set flip-flop 352 is not exported to H level signal.So, shielding part 351a switch element Q301 is switched to specified time limit after disconnection during T2 in, the zero-signal (H level signal) from zero current detection portion 351 is stopped.

Here, described in the problem that will solve in invention, in the case of the temporary decline of output voltage of AC power AC, even if switch element Q301 switches to conducting, in inductor L301, do not put aside sufficient energy yet.Therefore, if switch element Q301 is switched to disconnection under the inadequate state of savings of the energy to inductor L301, put aside energy in inductor L301 insufficient, so the energy of savings is by abrupt release.By zero current detection portion 351, this situation detected and switch element Q301 is switched to conducting, switch element Q301 carries out ON/OFF repeatedly with the very short cycle, and switch element Q301 is likely heated and damages.

So, in the present embodiment, by shielding part 351a is set as described above, in the temporary decline of output voltage of alternating voltage AC and do not put aside sufficient energy in inductor L301 in the situation that, in during specified time limit T2, the action of exporting zero-signal from zero current detection portion 351 is stopped, preventing that switch element Q301 moment from switching to conducting.So, in the output voltage of AC power AC, occurred abnormal, can prevent that switch element Q301 is with very short cycle switched conductive/disconnection, can prevent the cause thermal damage of the switch element Q301 that the increase of switching losses causes.Therefore, can realize the higher device of the less reliability of fault.

(execution mode 14)

Below, with reference to accompanying drawing to describing about the supply unit of embodiments of the present invention 14.But basic structure and the execution mode 13 of present embodiment are common, so give identical label and description thereof is omitted for common part.Present embodiment, as shown in Figure 52, is characterized in that, ono shot pulse generating unit 351b, AND element AND301, NOT element NOT301 are not set in zero current detection portion 351.And, the output signal of the 11st operational amplifier OP311 is directly inputted in AND element 302, and the output signal of rest-set flip-flop 352 is input in the gate terminal of switch element Q309.

In addition, in execution mode 13, in the input prime of the 2nd operational amplifier OP302, be provided with filter portion 355, but between the lead-out terminal of the 2nd operational amplifier OP302 and rest-set flip-flop 352, be provided with filter portion 355 in the present embodiment.And then, the filter portion 355 of present embodiment as shown in Figure 53, by gate terminal via NOT element NOT302 be transfused to the output signal of the 2nd operational amplifier OP302 the switch element Q310 being formed by MOSFET, be connected to switch element Q310 drain terminal on capacitor C312 and capacitor C312 supplied with to the 4th constant current source Iref304 of electric current form.

In filter portion 355, if the output signal of the 2nd operational amplifier OP302 is H level, switch element Q310 switches to disconnection, starts the charging of capacitor C312.And if the charging voltage of capacitor C312 exceedes assigned voltage, the reseting terminal input H level signal to rest-set flip-flop 352, makes switch element Q301 switch to disconnection via the 1st drive division 350.Here, be made as to Tf during filtering the time that reaches assigned voltage from starting being charged to of capacitor C312.In addition, during filtering, Tf is determined by the electric current flowing out from the 3rd constant current source Iref303 and the static capacity of capacitor C312.

Below, utilize the action of the zero current detection portion 351 of Figure 54 to present embodiment to describe.First, at switch element Q301, be under the state disconnecting, if if the savings energy of inductor L301 discharges, the secondary coiling voltage of inductor L301 is lower than the supply voltage of the 9th reference voltage source Vref309, from the 11st operational amplifier OP311 output H level signal (with reference to Figure 54 (c), Figure 54 (d)).Conventionally, in the off period of switch element Q301, because switch element Q309 is off-state, so capacitor C311 is charged by the 3rd constant current source Iref303, because charging voltage exceedes the 10th reference voltage source Vref310, so from the 12nd operational amplifier OP312 output H level signal.So, by the output signal of the 11st operational amplifier OP311 and the output signal of the 12nd operational amplifier OP312, make the output signal of AND element AND1 become H level, the terminal that arranges to rest-set flip-flop 352 is inputted H level signal, via the 1st drive division 350, switch element Q301 is switched to conducting (with reference to Figure 54 (a)).

If switch element Q301 switches to conducting, the electric current that flows through switch element Q301 increases and rises to the input voltage of the 2nd operational amplifier OP302.And, if this input voltage exceedes setting (output voltage of multiplier 353), after Tf during above-mentioned filtering, to the reseting terminal input H level signal of rest-set flip-flop 352, via the 1st drive division 350, make switch element Q301 switch to disconnection (with reference to Figure 54 (a), Figure 54 (b)).If switch element Q301 switches to disconnection, the output signal of rest-set flip-flop 352 becomes L level, so switch element Q309 switches to disconnection, starts the charging (with reference to Figure 54 (e)) of capacitor C311.

The charging voltage of this capacitor C311 is same with execution mode 13, till the supply voltage that arrives the 10th reference voltage source Vref310, needs T2 specified time limit.So, shielding part 351a switch element Q301 is switched to specified time limit after disconnection during T2 in, the zero-signal (H level) from zero current detection portion 351 is stopped.

In addition, to the input voltage of the 2nd operational amplifier OP302 becoming 0V (with reference to Figure 54 (b)) after Toff through time of delay from the charging that starts capacitor C311.This time of delay Toff be the driving signal exported from the 1st drive division 350 become L level time be carved into the actual delay that switches to disconnection of switch element Q301 and cause.

In addition, at Tf during above-mentioned filtering, than time of delay, the in the situation that Toff being long, can there is not especially problem, but at Tf during above-mentioned filtering, problem likely occur than time of delay, Toff was short in the situation that.; in the H level signal by the 2nd operational amplifier OP302, rest-set flip-flop 352 is resetted after input; the driving signal of exporting at the 1st drive division 350 becomes the timing of L level, and the grid current of switch element Q301 is superimposed in the input signal of the 2nd operational amplifier OP302.If the secondary coiling voltage at this moment inductor L301 does not switch to positive voltage, momentary reset input is disengaged, and in switch element Q301, trembles, and likely switch element Q301 is applied to excessive stress.

In order to prevent this situation, ono shot pulse generating unit 351b is generally set as execution mode 13, in the d/d timing of savings energy of inductor L301, generate ono shot pulse, use this ono shot pulse that switch element Q301 is switched to conducting.But, if use ono shot pulse generating unit 351b, have circuit structure to become complicated problem.

So, in the present embodiment, T2 specified time limit of shielding part 351a is set as longer than Tf during filtering.Therefore, even if the grid current of switch element Q301 is superimposed in the input signal of the 2nd operational amplifier OP302 as described above, in during this timing T2 specified time limit, so do not have capacitor C311 fully to be charged.Thereby, from the 12nd operational amplifier OP312, do not export H level signal, in during specified time limit T2, the output signal of AND element AND2 is always L level, thus not can to rest-set flip-flop 352 terminal input H level signal is set, can prevent from trembling in switch element Q301.

So, in the present embodiment, do not need ono shot pulse generating unit 351b is set as execution mode 13, so can make circuit structure simplify, can realize fault still less and the higher device of reliability.

(execution mode 15)

Below, utilize accompanying drawing to describing about the supply unit of embodiments of the present invention 15.But basic structure and the execution mode 13 or 14 of present embodiment are common, so for giving identical label and description thereof is omitted in common position.In addition, the control circuit 303 of present embodiment is formed in DC power control circuit 305, startup portion 330, control power supply comparing section the 331, the 1st control power supply generating unit the 332, the 3rd control power supply generating unit 333 on same semiconductor substrate and forms.

Present embodiment is as shown in Figure 55, possesses the output voltage that is located in DC power control circuit 305 and judges DC power supply circuit 301 whether lower than the low judging part 356 of voltage of the low-voltage of the regulation lower than the assigned voltage of hope size (hereinafter referred to as " target voltage "), detect the life tests circuit 307 in the life-span of discharge lamp La, be located in action initialization circuit 304 and the 1st abnormal judging part 344 that the action of DC power control circuit 305 and converter control circuit 306 is stopped of the testing result based on life tests circuit 307, and be located in action initialization circuit 304 and the 2nd abnormal judging part 345 that the action of DC power control circuit 305 and converter control circuit 306 is stopped of the judged result based on the low judging part 356 of voltage.In addition, just passable as long as life tests circuit 307 can detect the life-span of discharge lamp La, be in the past known, so omit detailed explanation here.In addition, in order to ensure the startability of discharge lamp La, process not carrying out in advance abnormal judgement between warming up period and between the starting period in the 1st abnormal judging part 345.

The low judging part 356 of voltage as shown in Figure 56, by non-reversion input terminal, be transfused to the detection voltage of output voltage test section 311 and in reversion, be transfused to the 13rd operational amplifier OP313 of the reference voltage of the 11st reference voltage source Vref311 in input terminal, the switch element Q311 consisting of MOSFET and the drain terminal that is inserted in switch element Q311 that is transfused to the output signal of the 13rd operational amplifier OP313 in gate terminal forms with the resistance R 17 between the 3rd control power supply generating unit 333.

In the low judging part 356 of voltage, detect the low-voltage of the regulation lower than target voltage and be judged as extremely, judged result is sent to the 2nd abnormal judging part 345.Particularly, the supply voltage of the detection voltage of output voltage test section 311 and the 11st reference voltage source Vref311 is compared in the 13rd operational amplifier OP313, if if detect voltage lower than the supply voltage of the 11st reference voltage source Vref311, the output voltage of DC power supply circuit 301 becomes the low-voltage of the regulation lower than target voltage, from the 13rd operational amplifier OP313 output L level signal.And, by this L level signal, make switch element Q311 switch to disconnection, by controlling power supply generating unit 333 from the 3rd, via resistance R 317, the 2nd abnormal judging part 345 is exported to H level signal, be judged as abnormal.

In addition, as long as the supply voltage of the 11st reference voltage source Vref311 is low just more passable than the supply voltage of the 1st reference voltage source Vref301 that the target voltage of the output voltage of DC power supply circuit 301 is determined.For example, the target voltage of the output voltage of DC power supply circuit 301 is that the supply voltage of 400V, the 1st reference voltage source Vref301 is 2.5V, in the case of the output voltage of DC power supply circuit 301 is dropped to 80% situation of desired value be judged as abnormal, the supply voltage of the 11st reference voltage source Vref311 is 2.0V.

Below, utilize accompanying drawing to describe the action of the low judging part 356 of voltage and the 2nd abnormal judging part 345.First, if the output voltage of DC power supply circuit 301 is low, the detection voltage of output voltage test section 311 is lower than the supply voltage of the 11st reference voltage source Vref311, the output signal of the 13rd operational amplifier OP313 becomes L level, and the 2nd abnormal judging part 345 is inputted to H level signal (with reference to Figure 57 (a), Figure 57 (b), Figure 57 (c)).In the 2nd abnormal judging part 345, if be transfused to H level signal, judge and in DC power supply circuit 301, occurred extremely, to control to transfer to the zero hour (with reference to Figure 57 (d), Figure 57 (e)) between the starting period during lighting a lamp.

And, in the case of the output voltage of DC power supply circuit 301 lower than the low-voltage of regulation during (corresponding to T3 specified time limit) than short between the starting period, the 2nd abnormal judging part 345 is controlled with from during transferring between the starting period and lighting a lamp.Like this, once by through between the starting period, go out even if discharge lamp La dodges,, as long as the output voltage of DC power supply circuit 301 recovers just discharge lamp La to be applied to sufficient starting resistor, so can make the sudden strain of a muscle of discharge lamp La go out, be not maintained yet.

On the other hand, during the output voltage of DC power supply circuit 301 is lower than the low-voltage of regulation (corresponding to T4 specified time limit.For example approximately 0.5 second) exceed (with reference to Figure 58 (a), Figure 58 (b), Figure 58 (c)) in the situation between the starting period, the 2nd abnormal judging part 345 is exported stop signal from stopping judging part 342 after passing through between the starting period, the action of the 1st drive division 350 and the 2nd drive division 360 is stopped, maintaining halted state (with reference to Figure 58 (d), Figure 58 (e), Figure 58 (f)).; judgement exists permanent abnormal or the power consumption of the designed capacity that exceedes DC power supply circuit 301 has occurred in load circuit 302 or fault etc. has occurred in detecting 311 parts is not the abnormal of immediate recovery forming output voltage in the input voltage of DC power supply circuit 301; but likely reach the fault that can not guarantee fail safe; the action of DC power control circuit 305 and converter control circuit 306 is stopped, maintaining halted state.

Below, utilize Figure 59 to describe the abnormal judgement processing in action initialization circuit 304.First, during transferring to and lighting a lamp, setpoint frequency setting signal, so that driving frequency becomes frequency f 3 (S401).Then, the output signal of low voltage judging part 356 is input in the 2nd abnormal judging part 345 (S402), and the output signal of life tests circuit 307 is input in the 1st abnormal judging part 344 (S403).In addition, after also can being first input in the 1st abnormal judging part 344, be input in the 2nd abnormal judging part 345.Then, first in the 2nd abnormal judging part 345, carry out abnormal judgement and process (S404), only in this abnormal judgement, do not have abnormal in the situation that, in the 1st abnormal judging part 344, to carry out abnormal judgement processing (S405).

Here, present embodiment is if close to the homophase action of the resonance frequency of resonant structure 321, and idle current is less, thus can reduce circuit loss, but the sudden strain of a muscle that the discharge lamp La lowly causing of the output voltage of DC power supply circuit 301 easily occurs is gone out.In the case, if life-span judgement, the i.e. abnormal judgement of the 1st abnormal judging part 344 with discharge lamp La are treated to preferentially, can be that discharge lamp La has reached the life-span by the erroneous judgement that knocks out of discharge lamp La, may maintain the problem stopping of the action of DC power control circuit 305 and converter control circuit 306.

So, by being treated to preferentially with the abnormal judgement of the 2nd abnormal judging part 345 as described above, can prevent from being judged as in the mistiming that knocks out of discharge lamp La the situation the stopping generation that discharge lamp La has reached the life-span, maintained the action of DC power control circuit 305 and converter control circuit 306.

If be judged as " having abnormal " in the abnormal judgement of the 2nd abnormal judging part 345 is processed, to transfer to (S406) between the starting period, setpoint frequency setting signal is so that driving frequency becomes frequency f 2 (S407).Then, to being equivalent to the time timing (S408) between the starting period, the then output signal (S409) to the low judging part 356 of the 2nd abnormal judging part 345 input voltage.In this moment, in the abnormal judgement processing (S410) of the 2nd abnormal judging part 345, be judged as " without abnormal ", during transferring to and lighting a lamp, setpoint frequency setting signal is so that driving frequency becomes frequency f 3.On the other hand, in the situation that being judged as " having abnormal ", make the action of DC power control circuit 305 and converter control circuit 306 stop (S411).

As mentioned above, in the case of the output voltage of DC power supply circuit 301 temporary low, make temporary the transferring between the starting period of action of DC power control circuit 305 and converter control circuit 306, in addition, in the case of the output voltage of DC power supply circuit 301 exceedes specified time limit low, be judged as and be not the abnormal of immediate recovery but likely reach the fault that can not guarantee fail safe, can maintain the stopping of action of DC power control circuit 305 and converter control circuit 306, so can improve the fail safe of device.

(execution mode 16)

Below, utilize accompanying drawing to describing about the supply unit of embodiments of the present invention 16.But basic structure and the execution mode 14 or 15 of present embodiment are common, so for giving identical label and description thereof is omitted in common position.Present embodiment, as shown in Figure 60, possesses the output voltage that is located in DC power control circuit 305 and judges DC power supply circuit 301 and whether exceedes 1st regulation superpotential voltage rising judging part 357, life tests circuit 307 and the 1st abnormal judging part 344 higher than target voltage.In addition, life tests circuit 307 and the 1st abnormal judging part 344 are structures same with execution mode 15.

Voltage rising judging part 357 as shown in Figure 61, by thering is the 3rd multiplexer circuit MP303 of a pair of transmission gate element being connected with the 12nd reference voltage source Vref312 and the 13rd reference voltage source Vref313 respectively and being transfused to the detection voltage of output voltage test section 311 and forming at the 14th operational amplifier OP314 that reversion is transfused to the output signal of the 3rd multiplexer circuit MP303 in input terminal in non-reversion input terminal.In addition, the supply voltage of the 13rd reference voltage source Vref313 (the 1st regulation overvoltage) is larger than the supply voltage of the 12nd reference voltage source Vref312 (the 2nd regulation overvoltage).The output signal of the 14th operational amplifier OP314 is imported in the reseting terminal of rest-set flip-flop 352 and is imported in an input terminal of OR element OR304.In addition, be transfused to the output signal of rest-set flip-flop 352 in another input terminal of OR element OR304, the output signal of OR element OR304 is imported in start portion 354 again.

If the output signal of start portion 354 OR element OR304 becomes L level again, start timing, if the time of timing exceedes Tr specified time limit, export H level signal.And, by this H level signal is input to arranging in terminal of rest-set flip-flop 352 via OR element OR303, via the 1st drive division 350, make switch element Q301 switch to conducting thus, restart the action of DC power control circuit 305.

Below, utilize Figure 62 to describe the action of voltage rising judging part 357.In voltage rising judging part 357, if the 1st regulation overvoltage higher than target voltage detected, be judged as extremely, make the action of DC power control circuit 305 stop.Particularly, the supply voltage of the detection voltage of output voltage test section 311 and the 13rd reference voltage source Vref313 is compared in the 14th operational amplifier OP314, if detect the supply voltage that voltage exceedes the 13rd reference voltage source Vref313, from the 14th operational amplifier OP314 output H level signal.And, this H level signal is input in the reseting terminal of rest-set flip-flop 352, via the 1st drive division 350, make switch element Q301 switch to disconnection, the action of DC power control circuit 305 stops (with reference to Figure 62 (a), Figure 62 (b), Figure 62 (c)).

Here, the output voltage of the 3rd multiplexer circuit MP303 is L level, to be the supply voltage of the 13rd reference voltage source Vref313 in the output signal of the 14th operational amplifier OP314, if but the output signal of the 14th operational amplifier OP314 be H level, if the output voltage of DC power supply circuit 301 becomes the 1st regulation overvoltage higher than target voltage, the output voltage of the 3rd multiplexer circuit MP303 is switched to the supply voltage of the 12nd reference voltage source Vref312.And, along with the action of DC power control circuit 305 stops, the output voltage of DC power supply circuit 301 declines, if the detection voltage of output voltage test section 311 lower than the supply voltage of the 12nd reference voltage source Vref312, the 2nd regulation overvoltage, the output signal of the 14th operational amplifier OP314 becomes L level (with reference to Figure 62 (b)).In this moment, because the output signal of rest-set flip-flop 352 is also L level, so the output signal of OR element OR304 is L level, starting timing in start portion 354 again.And, if the time of timing exceedes Tr specified time limit, from start portion 354 again, export H level signal, by this H level signal, restart the action (with reference to Figure 62 (c), Figure 62 (d)) of DC power control circuit 305.

In the past, at the output voltage of DC power supply circuit 301, exceeded in the superpotential situation of regulation the action of DC power control circuit 305 is stopped, and if exceed Tr specified time limit by time of start portion 354 timing again, controlled to restart.In the case, need imagination from the action that stops DC power control circuit 305 to the steady needed time of output voltage and start portion 354 again, set Tr specified time limit (for example 100～200 μ s).This specified time limit, Tr was owing to being determined by the capacity that is located at the capacitor on the chip that forms again start portion 354, so for by specified time limit Tr set compared with long and have to make the capacity of capacitor to become large, have chip area to increase and the problem that maximizes in start portion 354 again.

So, in the present embodiment, as mentioned above, in voltage rising judging part 357, when the action of DC power control circuit 305, whether the output voltage that by the detection voltage ratio of the supply voltage of the 13rd reference voltage source Vref313 and output voltage test section 311, judges DC power supply circuit 301 has exceeded the 1st regulation overvoltage higher than target voltage.And, when the action of DC power control circuit 305 stops, whether the output voltage that by the detection voltage ratio of the supply voltage of the 12nd reference voltage source Vref312 and output voltage test section 311, judges DC power supply circuit 301 has dropped near target voltage.

So, when the action of DC power control circuit 305 stops, as long as near moment output voltage drops to target voltage by start portion 354 timing Tr specified time limit are just passable again, so can significantly shorten Tr specified time limit compared with the situation in the past of start portion 354 timing again with when the action of DC power control circuit 305 stops.Thereby the capacity of the capacitor of setting Tr specified time limit is less just enough, makes start portion 354 miniaturizations so can reduce chip area again.

As mentioned above, can make circuit miniaturization in the present embodiment and realize the still less higher supply unit of reliability of fault.In addition, also can combine in the present embodiment the structure of low judging part the 356, the 2nd abnormal judging part 345 of voltage of recording in execution mode 16.In the case, can realize the still less higher supply unit of fail safe of fault.

And then, present embodiment possess for when the startup of discharge lamp La by each filament of discharge lamp La preheating part 20 of preheating respectively.Preheating part 20 possess have on one end is connected to power converter portion 2 tie point of switch element Q10, Q20 via capacitor C6 and the once coiling of other end ground connection and respectively and the series circuit of capacitor C4, C5 be connected to the transformer Tr1 of two secondaries coilings between the two ends of each filament of discharge lamp La.

And then present embodiment possesses each switch element Q10, the Q12 of power converter portion 2 is connected via resistance R 1, R2 respectively and disconnected and driven each switch element Q10, the Q12 of power converter portion 2 and from power converter portion 2, discharge lamp La is supplied with the drive division 31 of alternating electromotive force and controls the sequential control portion 41 of the frequency of the alternating electromotive force of discharge lamp La being exported from power converter portion 2 by controlling the frequency of action of drive division 31 by conducting.

Drive division 31 is located at the driving consisting of high-withstand-voltage integrated circuit (HVIC) with in integrated circuit 3, and sequential control portion 41 is located at the control consisting of the integrated circuit that is called microcontroller (microcomputer) with in integrated circuit 4.As controlling with integrated circuit 4, as long as use the magnitude of voltage of input and output to only have two grades, do not comprise the structure of A/D converter and D/A converter, just the power consumption of inhibitory control in integrated circuit 4 preferably.

In addition, present embodiment possesses and after the action of drive division 31 starts, from power converter portion 2, is supplied with electric power and export as the driving power portion 5 driving with the direct current power of the power supply of integrated circuit 3.Driving power portion 5 has outlet side capacitor (not shown) and is connected on the tie point of switch element Q10, Q20 of power converter portion 2 and by the charging circuit (not shown) of outlet side capacitor charging, using the both end voltage of outlet side capacitor as output voltage.The state that the both end voltage of outlet side capacitor is stable starting through time enough from the action of drive division 31, the both end voltage of outlet side capacitor is that the output voltage of driving power portion 5 is for example 10V.

And then, driving with in integrated circuit 3, be respectively equipped with before the action of drive division 31 starts, from DC power supply portion 1, supplied with electric power and export as the startup portion 32 of the direct current power of the power supply of driving power portion 5 and from driving power portion 5, supplied with electric power and the output voltage of driving power portion 5 be more than the reference voltage of regulation during generate as controlling with the direct current power of for example 5V of the power supply of integrated circuit 4 and be supplied to the control power supply unit 33 of control in integrated circuit 4.

If explained, as shown in Figure 3, startup portion 32 has on the output of high-voltage side that one end is connected to DC power supply portion 1 and the other end is connected to the impedance component Z1 on the output of driving power portion 5 via the 1st switch element Q101.That is, during the 1st switch element Q101 conducting of startup portion 32 in, the output voltage V dc of DC power supply portion 1 is exported to driving power portion 5 via impedance component Z1 and the 1st switch element Q101, thus by the output capacitor charging of driving power portion 5.Above-mentioned the 1st switch element Q101 consists of the withstand voltage field-effect transistor of height of N-shaped raceway groove, the grid of the 1st switch element Q101 is connected on the tie point of DC power supply portion 1 and impedance component Z1 via resistance R 101, and via the series circuit of diode D101 and Zener diode ZD2 the parallel circuits ground connection with the 2nd switch element Q102 being formed by the field-effect transistor of n raceway groove.In addition, startup portion 32 has respectively by 4 divider resistances of the output voltage of driving power portion 5 (hereinafter referred to as " driving voltage ") Vcc2 dividing potential drop, from tie point different 3 kinds of detection voltage Va, Vb, the Vc of output voltage (voltage ratio) respectively of these divider resistances.And then startup portion 32 possesses in reversion and is transfused to the comparator C P1 on the 1st reference voltage Vr1 of regulation and lead-out terminal be connected to the 2nd switch element Q102 grid via logic and circuit OR1 in input terminal.In the non-reversion input terminal of comparator C P1, via the multiplexer TG1 that uses transmission gate circuit to form, be transfused to and detect voltage Vb, Vc.Above-mentioned multiplexer TG1 is connected on the lead-out terminal of comparator C P1, in during the output H level being configured at comparator C P1, the 2nd low detection voltage (hereinafter referred to as " the 2nd detects voltage ") Vb is input in the non-reversion input terminal of comparator C P1, in during the output L of comparator C P1 level, minimum detection voltage (hereinafter referred to as " the 3rd detects voltage ") Vc is input in the non-reversion input terminal of comparator C P1.

Use Fig. 4 that the action of startup portion 32 is described.After power supply is just switched on, by the output of comparator C P1, it is L level, by the 3rd, detect voltage Vc and be input in the non-reversion input terminal of comparator C P1, and by the 2nd switch element Q102 is disconnected, by the Zener voltage of Zener diode ZD2 by the 1st switch element Q101 conducting.During the 1st switch element Q101 conducting, the outlet side capacitor of driving power portion 5 is supplied to the output power of DC power supply portion 1 and is charged by the impedance component Z1 via startup portion 32 and the 1st switch element Q101, and driving voltage Vcc2 rises gradually thus.If the final the 3rd detects voltage Vc, reach the 1st reference voltage Vr1, the output of comparator C P1 becomes H level.So, to the input voltage of non-reversion input terminal, be changed to than the 3rd and detect the 2nd detection voltage Vb that voltage Vc is high, and the 2nd switch element Q102 is switched on and the 1st switch element Q101 is disconnected, and the supply of the electric power from startup portion 32 to driving power portion 5 is stopped thus.In this moment, also do not start the action of drive division 31, from power converter portion 2, driving power portion 5 is not supplied with to electric power, so by the electric discharge of output capacitor, driving voltage Vcc2 starts to decline.If the final the 2nd detects voltage Vb, reach the 1st reference voltage Vr1, the output of comparator C P1 becomes L level again, the output voltage of driving power portion 5 starts to rise, if then the 3rd detection voltage Vc reaches the 1st reference voltage Vr1, the output of comparator C P1 becomes H level again.Then, from DC power supply portion 1, supply with such direct current power shown in Fig. 4 (a), and shown in Fig. 4 (e) during stopping enforcement division 34 (aftermentioned) and stopping to the input L level of logic and circuit OR1 and drive division 31, by repeatedly carrying out of above-mentioned action, the grid voltage of the 1st switch element Q101 changes as shown in Fig. 4 (c), driving voltage Vcc2 is as shown in Fig. 4 (b), the 3rd, detect voltage Vc and become the such upper voltage limit of the 1st reference voltage Vr1, and the 2nd detect voltage Vb and become between the such lower voltage limit of the 1st reference voltage Vr1 and repeatedly change up and down.

Here, driving with in integrated circuit 3, be provided with control respectively drive division 31 and startup portion 32 stop enforcement division 34.The output that stops enforcement division 34 is imported in logic and circuit OR1, in during stopping the output L level of enforcement division 34, drive division 31 is stopped and the electric power from startup portion 32 to driving power portion 5 is supplied with to conducting, but in during stopping the output H level of enforcement division 34, by haveing nothing to do and disconnect the electric power from startup portion 32 to driving power portion 5 is supplied with and disconnected by the 2nd switch element Q102 conducting and by the 1st switch element Q101 with the output of comparator C P1.Wherein, in during stopping the output H level of enforcement division 34, by drive division 31 move (generating the output of the driving use of switch element Q10, Q20 such shown in Fig. 4 (f)) carry out electric power from from power converter portion 2 to driving power portion 5 and supply with.

In addition, driving with in integrated circuit 3, be provided with from driving power portion 5, supplied with electric power and the output voltage of driving power portion 5 be more than the reference voltage of regulation during generate as controlling with the direct current power of assigned voltage (hereinafter referred to as " control the voltage ") Vcc1 of the power supply of integrated circuit 4 the control power supply unit 33 that control is supplied with integrated circuit 4.If explained, control power supply unit 33 and possess the comparator C P2 that is transfused to the highest detection voltage (hereinafter referred to as " the 1st detects the voltage ") Va in the detection voltage that the divider resistance of startup portion 32 exports and is transfused to the 1st reference voltage Vr1 in non-reversion input terminal in reversion input terminal, be connected to constant current circuit Ir1 between output and the earthing potential of driving power portion 5 and the series circuit of Zener diode ZD3, base stage is connected on the tie point of constant current circuit Ir1 and Zener diode ZD3 and collector electrode is connected on the output of driving power portion 5 and emitter is connected to the transistor Q103 controlling by the npn type on integrated circuit 4 as the output of controlling power supply unit 33, and be connected in that the field-effect transistor by N-shaped raceway groove on Zener diode ZD3 forms in parallel and grid is connected to the switch element Q104 on the lead-out terminal of comparator C P2.; as shown in Fig. 4 (d), be configured to; in only during the 1st detects voltage Va to exceed the 1st reference voltage Vr1, to controlling with integrated circuit 4, export and control voltage vccs 1; in during the 1st detection voltage Va is lower than the 1st reference voltage Vr1, does not export and control voltage vcc 1 (output voltage of controlling power supply unit 33 is roughly 0), driving voltage when the 1st detection voltage Va is the 1st reference voltage Vr1 is said reference voltage.Here, from driving, use integrated circuit 3 to controlling the circuit of controlling voltage vcc 1 with integrated circuit 4 outputs via noise elimination electricity consumption container C 51 ground connection.

In addition, driving with in integrated circuit 3, be provided with the oscillating portion 35 of the square wave of the output frequency corresponding with the output of sequential control portion 41, drive division 31 disconnects with the frequency conducting of the output of oscillating portion 35 the switch element Q10, the Q20 that control power converter portion 2.And then, driving with in integrated circuit 3, be provided with and stopped the report voltage vcc 3 that enforcement division 34 is controlled and output stipulates in the action of drive division 31 and the driving power portion 30 in the action of drive division 31, output being stopped.The circuit structure same with controlling power supply unit 33 for example can be made by driving power portion 30.Report voltage vcc 3 by the operate condition of drive division 31 in order to report also to control integrated circuit 4 and to export controlling with integrated circuit 4.In addition, oscillating portion 35 is using above-mentioned report voltage vcc 3 as power supply.That is, stop enforcement division 34 by making the electric power supply from report power supply unit 30 to oscillating portion 35 stop making oscillating portion 35 and drive division 31 to stop respectively.

Oscillating portion 35 as shown in Figure 5, possess that non-reversion input terminal is connected in sequential control portion 41 via resistance R 103 and lead-out terminal is connected on reversion input terminal and via two resistance R 106 with controlling the parallel circuits ground connection of electricity consumption container C 103 via resistance R 104, R102 ground connection and reversion input terminal are connected to the voltage follower OP1 consisting of operational amplifier on lead-out terminal, and in non-reversion input terminal, be transfused to the 2nd reference voltage Vr2 of regulation and the input terminal that reverses is connected to the control operational amplifier OP2 on the lead-out terminal of voltage follower OP1 via resistance R 106.The lead-out terminal of this operational amplifier 102 is connected on the grid of charging switch element Qc, between this charging is connected in the charging current mirroring circuit CM1 that is transfused to respectively report voltage vcc 3 in each input output with switch element Qc and resistance R 102, above-mentioned charging with another output of current mirroring circuit CM1 via vibration electricity consumption container C 102 ground connection.In addition, oscillating portion 35 possesses the 1st electric discharge switch element Qd that being connected to via grid in input charging forms with the field-effect transistor by p-type raceway groove on an above-mentioned output of current mirroring circuit CM1 and is transfused to and reports that voltage vcc 3 and connecting vibrates electricity consumption container C 102 and each output is distinguished the electric discharge current mirroring circuit CM2 of ground connection on another input.And then oscillating portion 35 possesses reversion input terminal and is connected in vibration electricity consumption container C 102 and in non-reversion input terminal the comparator C P3 that is transfused to a side of the 4th reference voltage Vr4 of the 3rd reference voltage Vr3 of regulation and the low regulation of Bi 3 reference voltage Vr3 via the multiplexer TG2 that uses transmission gate circuit to form.On above-mentioned multiplexer TG2, connecting the lead-out terminal of comparator C P3, in during the output H level being configured at comparator C P3, the 3rd reference voltage Vr3 is input in the non-reversion input terminal of comparator C P3, the 4th reference voltage Vr4 is input in the non-reversion input terminal of comparator C P3 in during the output L of comparator C P3 level.In addition, in electric discharge, use on current mirroring circuit CM2, the 2nd electric discharge switch element Q105 that is being connected in parallel, the 2nd electric discharge consists of the field-effect transistor of N-shaped raceway groove with switch element Q105, and grid is connected on the lead-out terminal of comparator C P3.

Action to oscillating portion 35 describes.In vibration electricity consumption container C 102, do not have under fully charged state, comparator C P3 is output as H level, thus, is transfused to the 3rd reference voltage Vr3, by switch element Q105 conducting in the non-reversion input terminal of comparator C P3.During this period, by being connected in the conducting of the 2nd electric discharge switch element Q105 on electric discharge current mirroring circuit CM2 in parallel, suppressed with the electric discharge of the vibration electricity consumption container C 102 of current mirroring circuit CM2 via electric discharge, by the charging with current mirroring circuit CM1 via charging, the both end voltage of vibration electricity consumption container C 102 rises gradually.If finally vibrated, the both end voltage of electricity consumption container C 102 reaches the 3rd reference voltage Vr3, the output of comparator C P3 becomes L level, input voltage to the non-reversion input terminal of comparator C P3 becomes the 4th reference voltage Vr4, and the 2nd electric discharge disconnects with switch element Q105.So, via electric discharge, with the discharging current of current mirroring circuit CM2, becoming than many via the charging current of charging current mirroring circuit CM1, the both end voltage of the electricity consumption container C 102 of vibrating is thus low gradually.And if the both end voltage of vibration electricity consumption container C 102 reaches the 4th reference voltage Vr4, the output of comparator C P3 becomes H level again, below repeats same action.Thus, the both end voltage of vibration electricity consumption container C 102 repeatedly changes up and down as shown in Fig. 6 (a) to the input voltage of the reversion input terminal of comparator C P3 between the 3rd reference voltage Vr3 and the 4th reference voltage Vr4, and the output of comparator C P3 becomes such square wave shown in Fig. 6 (b).And then oscillating portion 35 has the output Shaping circuit 35a that the output Shaping of comparator C P3 is exported to drive division 31.Output Shaping circuit 35a has the 1st rectangular signal generating unit (not shown) that generates the 1st rectangular signal as shown in Fig. 6 (c) by the output of comparator C P3 being carried out to for example two divided-frequency, generation is by the 2nd rectangular signal generating unit (not shown) of the 2nd rectangular signal of the output reversion of the 1st rectangular signal, and drive signal and drive signal to drive signal and the 2nd to drive signal to output to respectively generating unit dead time (not shown) drive division 31 by the 1st by making the timing of conducting of the 2nd rectangular signal generate the 2nd with above-mentioned same delay by making td dead time of constant time lag regulation of conducting (reversion from L level to H level) of the 1st rectangular signal generate shown in Fig. 6 (d) the such the 1st.Drive division 31 has a switch element Q10 making power converter portion 2 conducting drive the 1st drive division 31a that the off period (during L level) of signal breaks and another switch element Q20 that makes power converter portion 2 conducting the 2nd drive division 31b that breaks at the off period (during L level) of the 2nd driving signal in the 2nd drives conduction period (during H level) of signal the 1st in the 1st drives conduction period (during H level) of signal.That is,, by above-mentioned dead time of generating unit, prevent that two switch element Q10, Q20 of power converter portion 2 are by while conducting.In said structure, for vibration electricity consumption container C 102, do not require extra high capability value, so vibration electricity consumption container C 102 can be in control with forming in integrated circuit 4.

Here, charging current and the discharging current of vibration electricity consumption container C 102 are respectively: higher less to controlling input voltage both end voltage higher, that control electricity consumption container C 103 with the reversion input terminal of operational amplifier OP2.That is, the above-mentioned the 1st drive signal and the 2nd drive the frequency of frequency, the i.e. action of drive division 31 of signal and the frequency of the alternating electromotive force to discharge lamp La output (hereinafter referred to as " and operating frequency) be: the both end voltage of controlling electricity consumption container C 103 is higher lower.

Control the time starting according to the supply from control voltage vcc 1 shown in Figure 64 (a) with the sequential control portion 41 of integrated circuit 4, the both end voltage of the control electricity consumption container C 103 shown in Figure 64 (e) is changed, thus after by the preheating action t1～t2 of each filament difference preheating of discharge lamp La, startup action t2～t3 that lighting a lamp of discharge lamp La started, then, transfer to the operating stably t3～t4 lighting a lamp of sustain discharge lamp La.For example, sequential control portion 41 is unit of exporting pwm signal such shown in Figure 64 (d) via resistance R 103 to controlling electricity consumption container C 103, by the duty ratio of this pwm signal, the both end voltage of controlling electricity consumption container C 103 is changed.Particularly, by making said PWM signal stop (in other words making above-mentioned duty ratio is 0) in preheating action t1～t2, improve above-mentioned duty ratio than starting action t2～t3 in operating stably t3～t4, make to control electricity consumption container C 103 the both end voltage stage rise, as shown in Figure 64 (f), make the interim decline of operating frequency f1～f3.That is, make operating frequency is the highest operating frequency f1 in t1～t2 is moved in preheating, starting in action t2～t3, is than the low operating frequency f2 of preheating action t1～t2, is than starting lower operating frequency f3 in action t2～t3 in operating stably t3～t4.In addition, the output of sequential control portion 41 is not limited to pwm signal, as long as making the signal of the both end voltage variation of controlling electricity consumption container C 103 just passable.Make operating frequency f1～f3 than being connected between the two ends of switch element Q20 of downside of power converter portion 2 and comprising that the resonance frequency of resonant circuit of discharge lamp La is high, be that operating frequency f1～f3 is lower, from power converter portion 2, the electric power of discharge lamp La output more increased.That is, by the stage of operating frequency f1～f3 as described above, decline, to interim the increasing of output power of discharge lamp La.In addition, the timing t 3 that starts to start the timing t 2 of action t2～t3 and start operating stably t3～t4 for example determines by timing respectively, and the duration of preheating action t1～t2 and the duration that starts action t2～t3 are roughly respectively necessarily.

In addition, stop enforcement division 34 and among the dwell time T1 of regulation from the output of the control voltage vcc 1 to control integrated circuit 4 starts, do not start the action of drive division 31.Thereby, the timing that starts preheating action t1～t2 become from start to control with the output of the control voltage vcc 1 of integrated circuit 4 through after the dwell time T1 stipulating.Make the elongated degree of sufficient electric discharge to controlling electricity consumption container C 103 of dwell time T1, thereby, even situation about again starting after operating stably t3～t4 is stopped at once, also in the dwell time T1 before the preheating action t1～t2 starting then, control fully the electric discharge of electricity consumption container C 103, so t1 does not have the excessive situation of output power from power converter portion 2 to discharge lamp La when the beginning of preheating action t1～t2.

Here, controlling with in integrated circuit 4, be provided with and be connected to the stop control unit 42 stopping in enforcement division 34.From controlling with the stop control unit 42 of integrated circuit 4 to driving the circuit that stops enforcement division 34 with integrated circuit 3 to be connected to the circuit of controlling voltage vcc 1 via resistance R 51.Stop control unit 42 is made as by the current potential of foregoing circuit the L level equating with earthing potential conventionally, when drive division 31 is stopped, and by the current potential of foregoing circuit being made as and the H level of controlling voltage vcc 1 and equating, the stopping of indication drive division 31.That is, during having indicated the stopping of drive division 31 in above-mentioned resistance R 51 not current flowing and power consumption not, reduced power consumption compared with being always configured in above-mentioned resistance R 51 situation of the structure of current flowing.And, stop enforcement division 34 and do not make drive division 31 move in during the output H of stop control unit 42 level.In the example of Figure 64, t4 will be maintained L level to the input (output of stop control unit 42) that stops enforcement division 34 when starting to control the end that outputs to operating stably t3～t4 of voltage vcc 1, from the output that starts to control voltage vcc 1, after dwell time T1, starting preheating action t1～t2 thus, but become H level to the input that stops enforcement division 34 after the output that starts to control voltage vcc 1, be then changed to L level, to the input that stops enforcement division 34 becomes L level through starting preheating action t1～t2 after dwell time T1.; strictly say be from control power supply unit 33 output control voltage vccs 1 and to the input that stops enforcement division 34, be L level state continuance moment of dwell time T1 start preheating action t1～t2, from finishing operating stably t3～t4 to then starting at least to guarantee stopping of dwell time T1 preheating action t1～t2.

And then, present embodiment possess output with by the power supply test section 165 of the direct voltage corresponding voltage of the output voltage smoothing of rectification part DB and for example by the divider resistance of the output voltage dividing potential drop of DC power supply portion 1 being formed and the higher DC power supply test section 167 of exporting higher voltage of the output voltage of DC power supply portion 1.

In addition, in the driving of present embodiment, use in integrated circuit 3, be provided with the circuit of the switch element Q1 for driving DC power supply portion 1.If explained, in driving, use in integrated circuit 3, be provided with the output wrong amplifier OP4 corresponding with the difference of the output voltage of DC power supply test section 167 with the 7th reference voltage Vr7 of regulation, by the multiplier 36a of the output multiplication of the output of power supply test section 165 and wrong amplifier OP4, the output and the non-reversion input terminal that in reversion input terminal, are transfused to multiplier 36a are connected to the comparator C P7 on the switch element Q1 of DC power supply portion 1 and the tie point of resistance R 5, in reseting terminal, be transfused to the flip-flop circuit 36b of the output of comparator C P7, and it is upper and according to the output of flip-flop circuit 36b and conducting disconnects the 36c of power drives portion of the switch element Q1 that drives DC power supply portion 1 via resistance R 4, to be connected to the switch element Q1 of DC power supply portion 1.

And then, on the inductor L1 of DC power supply portion 1, being provided with 2 coilings of one end ground connection, the other end of these 2 times coilings is connected to be located at and drives with on the 36d of zero current detection portion in integrated circuit 3.The 36d of zero current detection portion is connected to arranging on terminal of flip-flop circuit 36c, based on exergonic the completing of voltage detecting inductor L1 of induction in above-mentioned 2 coilings, to flip-flop circuit 36b when exergonic the completing of inductor L1 being detected terminal input pulse is set.

Thus, by periodically conducting disconnection driving of the switch element Q1 of DC power supply portion 1, its duty ratio of FEEDBACK CONTROL, so that the output voltage of DC power supply portion 1 becomes the target voltage of regulation.This target voltage is to make the output voltage of DC power supply test section 167 become the voltage of the 7th reference voltage Vr7.

And then present embodiment possesses the parameter that changes when the end of lifetime of discharge lamp La the output life tests portion 63 corresponding to the voltage of the parameter detecting of detecting.Particularly, the asymmetrical current producing in discharge lamp La detects as above-mentioned parameter in the life tests portion 63 of present embodiment, and output is corresponding to its voltage.

In addition, controlling with in integrated circuit 4, be provided with output based on life tests portion 63 and judge whether to be the end of lifetime state of the abnormality that is end of lifetime as discharge lamp La and will corresponding to the output of judged result, to be input to the discharge lamp judging part 43 in stop control unit 42.That is, discharge lamp judging part 43 is the abnormal judging parts of load-side in technical scheme.

If explained, as shown in figure 25, life tests portion 63 possesses that the inductor L2 that one end is connected to power converter portion 2 via a filament of resistance R 111 and discharge lamp La is upper, the capacitor C106 of other end ground connection and the parallel circuits of resistance R 113.In addition, capacitor C106 is via negative electrode is connected on life-span judging part 43 towards the diode D103 of capacitor C106, and the tie point of this diode D103 and life-span judging part 43 is connected on the output (controlling voltage vcc 1) of controlling power supply unit 33 via resistance R 112.

Here, in the situation that discharge lamp La is not end of lifetime, in the lighting a lamp of discharge lamp La, electric current (hereinafter referred to as " the inflow current ") Idc+ from power converter portion 2 to life tests portion 63 and the electric current from life tests portion 63 to power converter portion 2 (hereinafter referred to as " outflow electric current ") Idc-are mutually roughly equal.Thus, the both end voltage of the capacitor C106 of life tests portion 63, the output voltage of life tests portion 63 is maintained roughly certain voltage (hereinafter referred to as " normal voltage "), and this normal voltage is about the voltage of controlling after voltage vcc 1 use resistance R112, R113 dividing potential drop.In addition, the inductor L2 of power converter portion 2 and the tie point of discharge lamp La are connected to via resistance R 114 on the output of high-voltage side of DC power supply portion 1.

On the other hand, if discharge lamp La becomes end of lifetime, by the consumption that is coated in the emitter on filament in discharge lamp La, in each filament, produce difference, one of above-mentioned electric current I dc+, Idc-becomes than another large (producing asymmetrical current), between the output voltage and above-mentioned normal voltage of life tests portion 63, there is poor corresponding to above-mentioned electric current I dc+, Idc-poor (size of asymmetrical current).For example, in the situation that outflow electric current I dc+ is more than inflow current Idc-, it is higher than above-mentioned normal voltage that the output voltage of life tests portion 63 becomes, otherwise in the situation that outflow electric current I dc+ is fewer than inflow current Idc-, the output voltage of life tests portion 63 becomes than above-mentioned normal electrical and forces down.

Life-span judging part 43 by the output voltage of life tests portion 63 with than the lower voltage limit of the high set upper limit voltage of normal voltage and the regulation forced down than normal electrical, compare respectively, if the output voltage of life tests portion 63 to be upper voltage limits following and lower voltage limit above, be judged as and be not end of lifetime state, if the output voltage of life tests portion 63 exceedes upper voltage limit or lower than lower voltage limit, be judged as end of lifetime state.For example, controlling voltage vcc 1, be 5V, normal voltage be 2.5V in the situation that, upper voltage limit is made as to 4V and lower voltage limit is made as to 1V.

And then, in driving, with in integrated circuit 3, the output being provided with based on DC power supply test section 167 judges whether the abnormality (hereinafter referred to as " the low state of direct voltage ") of the output voltage deficiency that is DC power supply portion 1 and exports the low judging part 37 of direct voltage corresponding to the voltage of judged result.That is, the low judging part 37 of direct voltage is the abnormal judging parts of mains side in technical scheme.If specifically described, the low judging part 37 of direct voltage as shown in figure 27, possesses and in non-reversion input terminal, is transfused to the output voltage of DC power supply test section 167 and is transfused in reversion the switch element Q107 that the FET by n channel-type on the lead-out terminal that the comparator C P8 of the 8th reference voltage Vr8 of the regulation lower than the 7th reference voltage Vr7 and grid be connected to this comparator C P8 forms in input terminal.One end ground connection of this switch element Q107 and in the other end via resistance R 32 be transfused to report voltage vcc 3, the tie point of this switch element Q107 and resistance R 32 as the output of the low judging part 37 of direct voltage be connected to control use integrated circuit 4 on.Above-mentioned the 8th reference voltage Vr8 is made as corresponding to 50%～80% of the 7th reference voltage Vr7 of target voltage.; the low judging part 37 of direct voltage when the output voltage of DC power supply test section 167 be that the 8th reference voltage Vr8 is not judged as the low state of direct voltage and output is made as to L level when above; when the output voltage of DC power supply test section 167 is judged as the low state of direct voltage than the 8th reference voltage Vr8 when low, output is made as to H level.For example, in the case of make the 8th reference voltage Vr8 be the 7th reference voltage Vr7 80%, when the output voltage fall short voltage of DC power supply portion 1 approximately 80% time be judged as the low state of direct voltage.

In addition,, controlling with in integrated circuit 4, be provided with the output proper transformation of low direct voltage judging part 37 is input to the judgement input part 144 in stop control unit 42.

The stop control unit 42 of present embodiment is at any time with reference to the output of life-span judging part 43 with judge the output of input part 144, if be judged as end of lifetime state by life-span judging part 43, to driving, with the output of integrated circuit 3, be made as H level, driving drive division 31 grades of integrated circuit 3 are stopped, and sequential control portion 41 is stopped.

In addition, stop control unit 42 is in the situation that being judged as the low state of direct voltage by the low judging part 37 of direct voltage, not to make as described above drive division 31 and sequential control portion 41 stop immediately, but control sequence control part 41 is to restart time T 5 (with reference to Figure 29) by what start that action stipulates, if be still judged as the low state of direct voltage after restarting time T 5, in this moment, same when being judged as end of lifetime state, to with the output of integrated circuit 3, be made as H level to driving, driving drive division 31 grades of integrated circuit 3 are stopped, and sequential control portion 41 is stopped.

The action of the present embodiment while representing to be judged as the low state of electric current in Figure 28 and Figure 29.In Figure 28 and Figure 29, be respectively that the time of (a) output voltage of representing DC power supply test section 167 changes, (b) represent the time of the output of the comparator C P8 of the low judging part 37 of direct voltage change, (c) represent the time of the output of the low judging part 37 of direct voltage change, time of the output of (d) order of representation control part 41 changes, (e) represent the time of operating frequency change, (f) represent that stop control unit 42 is for driving the time with the output of integrated circuit 3 to change.In the example of Figure 28, by the low state of direct voltage (being that the low judging part of direct voltage is the state of H level) than restarting the 4 interior end of the short time T of time T 5, that does not carry out that stop control unit 42 implements stops, and is starting operating stably after restarting time T 5 again.In addition, Figure 29 represents to have been reached and restarted time T 5, carried out the action in situation about stopping that stop control unit 42 implements by the duration of the low state of direct voltage.In the present embodiment, driving makes the 36c of power drives portion also stop by the enforcement division 34 that stops of integrated circuit 3 when stop control unit 42 is output as H level, in Figure 29, continuing after the end of the startup action of restarting time T 5, due to stopping of the 36c of power drives portion, the output voltage of the output voltage of DC power supply portion 1 and DC power supply test section 167 declines.

In addition, the in the situation that of making immediately drive division 31 and the 36c of power drives portion stop when being judged as the low state of direct voltage, the low state of direct voltage for example, because instantaneous power failure etc. cause, can not make discharge lamp La light a lamp even if eliminated at short notice.

To this, in the present embodiment, by when being judged as the low state of direct voltage, startup action being restarted to time T 5 as described above, in the case of going out, the low state discharge lamp of the direct voltage La sudden strain of a muscle of short time as described above can make discharge lamp La again light a lamp.In addition, after the end of above-mentioned startup action of restarting time T 5, be judged as the low state of direct voltage drive division 31 and the 36c of power drives portion are stopped, even so in the case of for example because of the output of the fault DC power supply test sections 167 such as short circuit do not reflect the output voltage of DC power supply portion 1 be always 0V such, also can avoid by wrong FEEDBACK CONTROL the electric stress of overaction on circuit element or discharge lamp La.

In addition, if there is the low state of direct voltage, consider for example sudden strain of a muscle of discharge lamp La of simultaneous to go out and lamp current is temporary becomes asymmetric and erroneous judgement is end of lifetime state, if carry out stopping of drive division 31 and the 36c of power drives portion by such erroneous judgement, likely can not carry out in fact the startup action of the judgement based on the low state of direct voltage as described above.In addition, for example, by making operating frequency fully leave and guarantee so-called slow phase side action with respect to the resonance frequency of the resonant circuit of power converter portion 2 and discharge lamp La formation, can avoid the sudden strain of a muscle as described above erroneous judgement causing of going out, if but like this, by idle current, increase and circuit loss increase, so not preferred.

So, the stop control unit 42 of present embodiment is in the case of judging both of end of lifetime state and the low state of direct voltage take the action judging based on the low state of direct voltage as preferential, do not carry out the action corresponding to the judgement of end of lifetime state in during being judged as the low state of direct voltage.Thus, can avoid the situation that the erroneous judgement because of end of lifetime state stops drive division 31 grades when the sudden strain of a muscle of discharge lamp La is gone out to occur.

In addition, in the control of present embodiment, use in integrated circuit 4, be provided with the clock portion 45 generating as the clock signal of the periodic signal of telecommunication, the frequency of clock signal is higher, control the more increase of power consumption with integrated circuit 4, the responsiveness of stop control unit 42 is faster on the other hand, faster for the response of abnormal generation.In the present embodiment, being conceived to especially need to be for the quick response that end of lifetime state and the low state of direct voltage occur in operating stably, clock portion 45, as shown in Figure 64 g, has adopted the clock frequency TB that makes in operating stably t3～t4 than the high structure of clock frequency TA in during other.Thus, by clock frequency being made as compared with high frequency TB and guaranteeing higher response speed in operating stably t3～t4, and drive division 31 stop middle clock frequency is made as to lower frequency TA, by suppressing power consumption, reduce the electric stress acting in startup portion 32, can make driving voltage Vcc2 stable.Here, clock frequency is just passable as long as be made as higher frequency TB in operating stably t3～t4, the t3 when timing that clock frequency is switched to higher frequency TB from lower frequency TA is not limited to the beginning of the such operating stably t3～t4 of Figure 64 (g), clock frequency is switched in other timings when t2 is to the beginning of operating stably t3～t4 in the time of also can be with beginning from preheating action t1～t2 t3.

In addition, also can be configured to the count section (not shown) that again starts the inferior counting number of action of sequential control portion having been carried out to the judgement based on the low state of direct voltage is set, at the above-mentioned number of times of being counted by this count section, reached set upper limit number of times (for example 5 times) even the rear low state of direct voltage that is judged as, sequential control portion 41 do not start yet start action and stop control unit 42 is made as H level by output, drive division 31 grades are stopped.

In addition, load is not limited to discharge lamp La, as long as the device that increases gradually of electric power that makes to supply with when starting just passable.

And then, also the 36d of zero current detection portion can be formed as shown in Figure 65 like that.If explained, the 36d of zero current detection portion of Figure 65 possesses reversion input terminal to be connected to the secondary coiling of inductor L1 of DC power supply portion 1 upper and in non-reversion input terminal, be transfused to the input comparator CP9 of the 9th reference voltage Vr9 of regulation, the single-shot trigger circuit OS that starts the output of the pulse of regulation amplitude when the output of input comparator CP9 when L level is reversed to H level, the non-inverter circuit INV of the output of output single-shot trigger circuit OS, the 1st logic integrated circuit AND1 of the logic product of the output of the output NAND circuit INV of output input comparator CP9, by the reservation electricity consumption container C 107 of charging as the constant current source Ir3 of power supply to control voltage vcc 1, by the FET of n channel-type, form and be connected in the switch element Q108 that retains in electricity consumption container C 107 and connecting the lead-out terminal of the 1st logic integrated circuit AND1 on grid in parallel, in reversion input terminal, be transfused to the 10th reference voltage Vr10 of regulation and on non-reversion input terminal, connecting the output comparator CP10 that retains electricity consumption container C 107, and the 2nd logic integrated circuit AND2 that the logic product of the output of the output of output comparator CP10 and single-shot trigger circuit OS is exported as the output of the 36d of zero current detection portion.

Utilize Figure 31 that the action of the 36d of zero current detection portion of Figure 65 is described.Consider the situation about changing to the input voltage of the 36d of zero current detection portion that winds the line for 2 times of the inductor L1 of DC power supply portion 1 as shown in (b) in Figure 31.So the output of input comparator CP9 becomes in Figure 31 shown in (c), the output of single-shot trigger circuit OS becomes in Figure 31 shown in (e).Retain electricity consumption container C 107 is discharged sharp via switch element Q108 when the 1st logic integrated circuit AND1 is output as H level, so during the output L of the 1st logic integrated circuit AND1 level, charged during the output L level of input comparator CP9 and in during the output H level of single-shot trigger circuit OS, make to rise gradually to the output voltage of output comparator CP10.Here, it is during the output of single-shot trigger circuit OS is the output H level of H level and output comparator CP10 that the 36d of zero current detection portion in Figure 31 shown in (g) is output as during H level, in Figure 31 the output of the output comparator CP10 shown in (f) during H level is reversed to the pulse duration amount of L level output tight, single-shot trigger circuit OS, thus, the output of the 36c of power drives portion becomes in Figure 31 output such shown in (a).As long as the output of output comparator CP10 is not H level, the output of the 36d of zero current detection portion does not just become H level, so to the input voltage of the 36d of zero current detection portion lower than the 9th reference voltage Vr9 after, in the retention time T6 of the regulation before the both end voltage that retains electricity consumption container C 107 has reached the 10th reference voltage Vr10, the output of the 36d of zero current detection portion does not become H level.In other words, as long as the duration to the input voltage of the 36d of zero current detection portion during lower than the 9th reference voltage Vr9 does not reach above-mentioned retention time T6, the output of flip-flop circuit 36b does not just become H level, thereby the switch element Q1 of DC power supply portion 1 is not switched on.

In addition, in DC power supply portion 1, by the contrary recovery time of spurious impedance and diode D1, after switch element Q1 has just been switched on, from the electric current (hereinafter referred to as " adverse current electric current ") of output capacitor C6, flows to and detect with in resistance R3.In addition, driving with in integrated circuit 3, if declined from the voltage (hereinafter referred to as " input supply voltage ") of AC power AC input to the input voltage of the reversion input terminal that is connected to the comparator C P7 on the reseting terminal of flip-flop circuit 36b, decline.And, at input supply voltage, with respect to the output of the low and above-mentioned comparator C P7 of above-mentioned countercurrent electric rheology, become H level, although do not put aside fully energy in inductor L1, switch element Q1 is also disconnected.In the case, although can, again by switch element Q1 conducting in the very short time, again be disconnected with above-mentioned same switch element Q1, can expect by this repeatedly and switch element Q1 is switched on disconnection with the shorter cycle.If switch element Q1 is switched on disconnection with the shorter cycle like this, the electric stress of overaction on switch element Q1.

With respect to this, in the structure of Figure 65, as mentioned above, as long as the duration to the input voltage of the 36d of zero current detection portion during lower than the 9th reference voltage Vr9 does not reach retention time T6, just not by the switch element Q1 conducting of DC power supply portion 1, the off-state that is switch element Q1 at least continues retention time T6, even so near the situation that the input voltage of the 36d of zero current detection portion fine changes as the right-hand member of Figure 31 also can avoid the switch element Q4 of DC power supply portion 1 because of the conducting disconnection lost of life in the cycle compared with short.

And then, in the example of Figure 65, the output of the 36d of zero current detection portion is connected to arranging on terminal of flip-flop circuit 36b via logic and circuit OR3, driving with in integrated circuit 3, be for example provided with, when monitoring the output of flip-flop circuit 36b and being L level more than lasting stipulated time of output of flip-flop circuit 36b (100 μ second) 36e of start portion again that terminal input pulse is set to flip-flop circuit 36 via above-mentioned logic and circuit OR3.

(execution mode 18)

Present embodiment stop enforcement division 34 as shown in Figure 66, output based on power supply test section 165 judges the low of input supply voltage, when being judged as input supply voltage when low, same while becoming H level with the output of stop control unit 42, output is made as to L level and make drive division 31 and report power supply unit 30 stop.

If specifically described, power supply test section 165 as shown in figure 20, is the unit that the direct voltage of capacitor smoothing is also used the output voltage of rectifier DB divider resistance dividing potential drop in output.In addition, stop enforcement division 34 and possess the 5th reference voltage Vr5 that is transfused to regulation in non-reversion input terminal and the input comparator CP4 that is transfused to the output voltage of power supply test section 165 in reversion input terminal, non-reversion input terminal is connected on stop control unit 42 and in reversion input terminal, is transfused to the input comparator CP5 of the 5th reference voltage Vr5, export above-mentioned two input comparator CP4, the logic of the output of CP5 and logic and circuit OR2, by being located at, drive the constant current source Ir2 charging by the outside delay electricity consumption container C 105 of integrated circuit 3, by the FET of n channel-type, form and be connected to side by side the switch element Q106 that postpones in electricity consumption container C 105 and be transfused to the output of logic and circuit OR2 in grid, and on non-reversion input terminal connection delay electricity consumption container C 105 and be transfused to the output comparator CP6 of the 6th reference voltage Vr6 of regulation in input terminal in reversion.This output comparator CP6 is output as during H level during drive division 31 and report power supply unit 30 move, during output report voltage vcc 3.

The above-mentioned action that stops enforcement division 34 is described.Stop enforcement division 34 using the control voltage vcc 1 of exporting from control power supply unit 33 as power supply, when starting, postpone thus the charging of electricity consumption container C 105 starts to start with the output of the control voltage vcc 1 from controlling power supply unit 33 simultaneously, when the both end voltage of delay electricity consumption container C 105 has reached the 6th reference voltage Vr6, the output of output comparator CP6 becomes H level, start thus the action of drive division 31 and the output of report voltage vcc 3, now, in startup portion 32, switch element Q101 is fixed to off-state.That is, use the output current of the constant current source Ir2 that stops enforcement division 34 to remove the charging interval T2 and the dwell time T1 that obtain the product of the capability value of delay electricity consumption container C 105 and the 6th reference voltage Vr6 consistent.

In addition, at the output voltage of power supply test section 165 lower than being output as H level the 5th reference voltage Vr5 or at stop control unit 42, by the output of any input comparator CP4, CP5, become H level and by switch element Q106 conducting, via switch element Q106, will postpone electricity consumption container C 105 discharges sharp, by postponing the both end voltage of electricity consumption container C 105, lower than the 6th reference voltage Vr6, the output of output comparator CP6 becomes L level, carries out stopping of drive division 31 and report voltage vcc 3.Here, time (hereinafter referred to as " the retention time ") T3 (with reference to Figure 21) that becomes L level from switch element Q106 being disconnected to the output of output comparator CP6 becomes enough short.

In Figure 21, represent an example of the action of present embodiment.In the example of Figure 21, in the output of the stop control unit 42 shown in Figure 21 (a), become the moment of L level, output voltage by the power supply test section 165 shown in Figure 21 (b) is lower than the 5th reference voltage Vr5, the output of an input comparator CP4 shown in Figure 21 (c) is H level, thereby the output of the logic shown in Figure 21 (d) and circuit 2 also becomes H level.If the output voltage of final power supply test section 165 exceedes the 5th reference voltage Vr5, by the output of logic and circuit OR2, become L level and switch element Q106 is disconnected, start to postpone the charging of electricity consumption container C 105.And then, if through charging interval T2, the both end voltage that postpones electricity consumption container C 105 reaches the 6th reference voltage Vr6, and the output of output comparator CP6 becomes H level, the output of the report voltage vcc 3 shown in action and Figure 21 (f) of beginning drive division 31.Then, if the output of power supply test section 165 declines, lower than the 5th reference voltage Vr5, in very short retention time T3, the output of output comparator CP6 becomes L level, here, the output of the action of drive division 31 and report voltage vcc 3 is stopped respectively.

In addition, in the present embodiment, as shown in Figure 67, when the duty ratio that sequential control portion 41 makes the pwm signal (Figure 67 (d)) of exporting to oscillating portion 35 is moved the beginning of t1～t2 from preheating t1 to start action t2～t3 end time t3 become gradually continuously large.Thus, the both end voltage of the control electricity consumption container C 103 shown in Figure 67 (e) becomes large with linearity in t1～t3 during above-mentioned, when the operating frequency shown in Figure 67 (f) is moved the beginning of t1～t2 from preheating the operating frequency f1 of t1 to the operating frequency f3 operating stably t3～t4 with linearity step-down.

(execution mode 19)

The structure of present embodiment and execution mode 2 are common, so give identical label and omit detailed diagram and explanation for common part.

In the present embodiment; as shown in Figure 68; driving with in integrated circuit 3, be provided with and judge whether it is the overvoltage condition that extremely uprises of the output voltage V dc of DC power supply portion 1 the low overvoltage protection portion 39 of output voltage that makes DC power supply portion 1 when being judged as overvoltage condition.

In addition, controlling with in integrated circuit 4, be provided with to as use supply unit time accumulative total accumulative total timing service time timing portion 46, by nonvolatile memory form and at least during power supply disconnects in keep the storage part 47 of accumulative total service time and before the accumulative total by 46 timing of timing portion reaches time device lifetime as the regulation in life-span of supply unit service time, make to be output as L level and after adding up service time to reach time device lifetime, make to be output as the report portion 48 of H level.By accumulative total for example timing in (being during drive division 31 moves) during being transfused to the next self-driven report voltage vcc 3 with integrated circuit 3 service time.

And then, driving with in integrated circuit 3, be provided with the report input part 38 of the output of input report portion 48.Report input part 38 is connected in overvoltage protection portion 39, and overvoltage protection portion 39 changes action according to the output of report portion 48.

If explained, as shown in figure 36, report input part 38 is connected to the 11st reference voltage Vr11, lead-out terminal that are transfused to regulation in report portion 48 and in non-reversion input terminal and via resistance R 33, is connected to control and forms by the comparator C 11 on the reversion input terminal of operational amplifier OP2 by reversion input terminal.Make the 11st reference voltage Vr11 lower and higher than the magnitude of voltage of the output of the L level of report portion 48 than the magnitude of voltage of the output of the H level of report portion 48.That is, report input part 38 is so-called inverter circuits, and the output of report input part 38 is the output reversion that the output of above-mentioned comparator C 11 makes report portion 48.

Overvoltage protection portion 39 possess in non-reversion input terminal, be transfused to the output of DC power supply test section 167 and reversion be transfused in input terminal regulation the 12nd reference voltage Vr12 comparator C P12 and the output of this comparator C P12 and the logic product of the output of report input part 38 are outputed to the logic integrated circuit AND3 in the reseting terminal of flip-flop circuit 36b.; when totally not reaching the time device lifetime service time; when the output voltage of DC power supply test section 167 exceedes the 12nd reference voltage Vr12; the overvoltage protection action that the switch element Q4 that carries out controlling DC power supply portion 1 by disconnection declines the output voltage V dc of DC power supply portion 1; after totally reaching device lifetime service time; output by report input part 38 becomes L level and the output of logic integrated circuit AND3 is fixed as to L level, does not carry out above-mentioned overvoltage protection action.

According to said structure, after totally reaching time device lifetime, by no longer carrying out overvoltage protection action, on the switch element Q4 of DC power supply portion 1, easily act on higher electric stress service time.Thereby, the possibility that switch element Q4 more first reaches the life-span than other voltage components uprises, so countermeasure of the easy establishment known current fuse of use (not shown) etc., in addition, because switch element Q4 reaches the life-span, the timing of fault is inhomogeneous, even so start the situation of the use of multiple supply units simultaneously, do not have the situation that discharge lamp La is turned off the light simultaneously when the life-span of these multiple supply units reaches yet.

In addition, overvoltage protection portion 39 is not limited to the above, also can replace and logic integrated circuit AND3 is set and is for example configured to like that as shown in figure 37, the 13rd reference voltage Vr13 of the 12nd reference voltage Vr12 and the high regulation of Bi 12 reference voltage Vr12 is input in comparator C P12 via the multiplexer TG3 that uses transmission gate circuit to form respectively, in during the output H of report portion 48 level, will be input to voltage in the reversion input terminal of comparator C P12 of overvoltage protection portion 39 and be made as the 13rd reference voltage Vr13 of the regulation higher than the 12nd reference voltage Vr12.If adopt this structure; by the voltage being input to after reaching the time device lifetime service time in accumulative total in the reversion input terminal of comparator C P12 of overvoltage protection portion 39, uprise; be difficult for carrying out overvoltage protection action, can obtain thus same effect.

Claims (10)

1. a discharge lamp ignition device, is characterized in that, possesses:

DC power supply portion, output direct current power;

Resonant structure forms resonant circuit together with discharge lamp;

Switch portion, comprises at least 1 switch element, follows the conducting of this switch element to disconnect switching being connected of DC power supply portion and resonant structure;

Drive division, disconnects driving by the switch element of switch portion being carried out to conducting, from resonant structure, discharge lamp is supplied with to alternating electromotive force;

Control part, by controlling the frequency of action of drive division, controls the frequency of the alternating electromotive force to discharge lamp output from resonant structure, and the action of this drive division refers to that by drive division, the switch element of switch portion being carried out to conducting disconnects the action driving;

Driving power portion is supplied with electric power from switch portion, and is exported direct current power after the action of drive division starts;

Startup portion is supplied with electric power from DC power supply portion, and driving power portion is supplied with to electric power before the action of drive division starts;

Control power supply unit, from driving power portion, supplied with electric power, at the output voltage of driving power portion, be more than the reference voltage of regulation during, generate as the direct current power of the power supply of control part and be supplied to control part; And

Storage part, this storage part consists of nonvolatile memory, deposit the ephemeral data using in the action of control part, the action of this control part refers to the action of controlling the frequency of the alternating electromotive force to discharge lamp output from resonant structure by the frequency of the action of control drive division;

As the operating frequency of the frequency of the action of above-mentioned drive division, corresponding to controlling, decide by the both end voltage of capacitor, this control makes both end voltage variation with capacitor corresponding to the output of control part;

Control part is when discharge lamp starts, after by each filament of discharge lamp, the preheating of preheating is moved respectively, the startup action that lighting a lamp of discharge lamp started, then makes the both end voltage of controlling with capacitor change, to transfer to the operating stably of lighting a lamp of sustain discharge lamp;

Drive division, after the output of the electric power from control power supply unit starts, does not start the action of drive division in the dwell time of regulation;

DC power supply portion is direct current power by the power converter being transfused to;

Above-mentioned discharge lamp ignition device possesses the low judging part of input voltage, and the low judging part of this input voltage judges whether it is the low state of input voltage to the input voltage deficiency of DC power supply portion;

During being judged as the low state of input voltage by the low judging part of input voltage, drive division does not start the action of drive division;

The deletion that remains on the ephemeral data in storage part is carried out in the action of drive division.

2. discharge lamp ignition device as claimed in claim 1, is characterized in that,

The action that reads out in drive division of leaving the ephemeral data in storage part in starts to carry out before.

3. a discharge lamp ignition device, is characterized in that, possesses:

DC power supply portion, output direct current power;

Resonant structure forms resonant circuit together with discharge lamp;

Switch portion, comprises at least 1 switch element, follows the conducting of this switch element to disconnect switching being connected of DC power supply portion and resonant structure;

Drive division, disconnects driving by the switch element of switch portion being carried out to conducting, from resonant structure, discharge lamp is supplied with to alternating electromotive force;

Control part, by controlling the frequency of action of drive division, controls the frequency of the alternating electromotive force to discharge lamp output from resonant structure, and the action of this drive division refers to that by drive division, the switch element of switch portion being carried out to conducting disconnects the action driving;

Driving power portion is supplied with electric power from switch portion, and is exported direct current power after the action of drive division starts;

Startup portion is supplied with electric power from DC power supply portion, and driving power portion is supplied with to electric power before the action of drive division starts;

Control power supply unit, from driving power portion, supplied with electric power, at the output voltage of driving power portion, be more than the reference voltage of regulation during, generate as the direct current power of the power supply of control part and be supplied to control part; And

Storage part, this storage part consists of nonvolatile memory, deposit the ephemeral data using in the action of control part, the action of this control part refers to the action of controlling the frequency of the alternating electromotive force to discharge lamp output from resonant structure by the frequency of the action of control drive division;

As the operating frequency of the frequency of the action of above-mentioned drive division, corresponding to controlling, decide by the both end voltage of capacitor, this control makes both end voltage variation with capacitor corresponding to the output of control part;

Control part is when discharge lamp starts, after by each filament of discharge lamp, the preheating of preheating is moved respectively, the startup action that lighting a lamp of discharge lamp started, then makes the both end voltage of controlling with capacitor change, to transfer to the operating stably of lighting a lamp of sustain discharge lamp;

Drive division, after the output of the electric power from control power supply unit starts, does not start the action of drive division in the dwell time of regulation;

DC power supply portion is direct current power by the power converter being transfused to;

Above-mentioned discharge lamp ignition device possesses:

The low judging part of input voltage, judges whether it is the low state of input voltage to the input voltage deficiency of DC power supply portion; And

Non-loaded judging part, judges whether it is the no-load condition that does not connect discharge lamp on resonant structure;

Be judged as no-load condition during being judged as the low state of input voltage by the low judging part of input voltage and by non-loaded judging part during, drive division does not start the action of drive division;

The deletion that remains on the ephemeral data in storage part is carried out in the action of drive division.

4. discharge lamp ignition device as claimed in claim 3, is characterized in that,

The action that reads out in drive division of leaving the ephemeral data in storage part in starts to carry out before.

5. a discharge lamp ignition device, is characterized in that, possesses:

DC power supply portion, output direct current power;

Resonant structure forms resonant circuit together with discharge lamp;

Switch portion, comprises at least 1 switch element, follows the conducting of this switch element to disconnect switching being connected of DC power supply portion and resonant structure;

Drive division, disconnects driving by the switch element of switch portion being carried out to conducting, from resonant structure, discharge lamp is supplied with to alternating electromotive force;

Control part, by controlling the frequency of action of drive division, controls the frequency of the alternating electromotive force to discharge lamp output from resonant structure, and the action of this drive division refers to that by drive division, the switch element of switch portion being carried out to conducting disconnects the action driving;

Driving power portion is supplied with electric power from switch portion, and is exported direct current power after the action of drive division starts;

Startup portion is supplied with electric power from DC power supply portion, and driving power portion is supplied with to electric power before the action of drive division starts;

Control power supply unit, from driving power portion, supplied with electric power, at the output voltage of driving power portion, be more than the reference voltage of regulation during, generate as the direct current power of the power supply of control part and be supplied to control part; And

Rectification part, this rectification part is to carrying out full-wave rectification from the alternating electromotive force of outside input;

As the operating frequency of the frequency of the action of above-mentioned drive division, corresponding to controlling, decide by the both end voltage of capacitor, this control makes both end voltage variation with capacitor corresponding to the output of control part;

Control part is when discharge lamp starts, after by each filament of discharge lamp, the preheating of preheating is moved respectively, the startup action that lighting a lamp of discharge lamp started, then makes the both end voltage of controlling with capacitor change, to transfer to the operating stably of lighting a lamp of sustain discharge lamp;

Drive division, after the output of the electric power from control power supply unit starts, does not start the action of drive division in the dwell time of regulation;

DC power supply portion comprises following Switching Power Supply, and this Switching Power Supply has on the tie point that series circuit that the output capacitor that is the output voltage of DC power supply portion by inductor and diode and both end voltage between the output of the rectification part of being connected to forms and one end be connected to above-mentioned inductor and above-mentioned diode and the series circuit consisting of switch element and resistance of other end ground connection;

Above-mentioned discharge lamp ignition device possesses:

Power drives portion, carries out conducting to the switch element of DC power supply portion and disconnects driving, so that the output voltage of DC power supply portion is remained necessarily; And

The abnormal judging part of DC power supply, detects the output voltage of DC power supply portion, and judges that DC power supply portion is normal or abnormal;

If it is abnormal to be judged as DC power supply portion by the abnormal judging part of DC power supply in operating stably, control part finishes operating stably and starts startup action again, in startup release again but by the abnormal judging part of DC power supply be judged as DC power supply portion abnormal, drive division is stopped.

6. discharge lamp ignition device as claimed in claim 5, is characterized in that,

Once power drives portion arrives the time before next conducting after the switch element of DC power supply portion is disconnected, more than being made as the retention time of regulation.

7. the discharge lamp ignition device as described in claim 5 or 6, is characterized in that, possesses:

Timing portion, carries out timing to accumulative total service time, and this accumulative total is at least added up timing service time in the action of drive division, and is not reset; And

Overvoltage protection portion, before reaching time device lifetime of regulation service time by the accumulative total of timing portion timing, the output voltage of working as DC power supply portion becomes assigned voltage and controls power drives portion so that the overvoltage protection action that the output voltage of DC power supply portion declines when above;

Overvoltage protection portion, after the accumulative total by the timing of timing portion reaches the time device lifetime service time, does not carry out overvoltage protection action.

8. a discharge lamp ignition device, is characterized in that, possesses:

DC power supply portion, output direct current power;

Resonant structure forms resonant circuit together with discharge lamp;

Switch portion, comprises at least 1 switch element, follows the conducting of this switch element to disconnect switching being connected of DC power supply portion and resonant structure;

Drive division, disconnects driving by the switch element of switch portion being carried out to conducting, from resonant structure, discharge lamp is supplied with to alternating electromotive force;

Control part, by controlling the frequency of action of drive division, controls the frequency of the alternating electromotive force to discharge lamp output from resonant structure, and the action of this drive division refers to that by drive division, the switch element of switch portion being carried out to conducting disconnects the action driving;

Driving power portion is supplied with electric power from switch portion, and is exported direct current power after the action of drive division starts;

Startup portion is supplied with electric power from DC power supply portion, and driving power portion is supplied with to electric power before the action of drive division starts;

Control power supply unit, from driving power portion, supplied with electric power, at the output voltage of driving power portion, be more than the reference voltage of regulation during, generate as the direct current power of the power supply of control part and be supplied to control part; And

Timing portion, this timing portion carries out timing to accumulative total service time, and this accumulative total is at least added up timing service time in the action of drive division, and is not reset;

As the operating frequency of the frequency of the action of above-mentioned drive division, corresponding to controlling, decide by the both end voltage of capacitor, this control makes both end voltage variation with capacitor corresponding to the output of control part;

Control part is when discharge lamp starts, after by each filament of discharge lamp, the preheating of preheating is moved respectively, the startup action that lighting a lamp of discharge lamp started, then makes the both end voltage of controlling with capacitor change, to transfer to the operating stably of lighting a lamp of sustain discharge lamp;

Drive division, after the output of the electric power from control power supply unit starts, does not start the action of drive division in the dwell time of regulation;

Control part, after reaching time device lifetime of regulation service time by the accumulative total of timing portion timing, makes pre-thermally operated Duration Ratio reach long before the time device lifetime service time by the accumulative total of timing portion timing.

9. a discharge lamp ignition device, is characterized in that, possesses:

DC power supply portion, output direct current power;

Resonant structure forms resonant circuit together with discharge lamp;

Switch portion, comprises at least 1 switch element, follows the conducting of this switch element to disconnect switching being connected of DC power supply portion and resonant structure;

Drive division, disconnects driving by the switch element of switch portion being carried out to conducting, from resonant structure, discharge lamp is supplied with to alternating electromotive force;

Control part, by controlling the frequency of action of drive division, controls the frequency of the alternating electromotive force to discharge lamp output from resonant structure, and the action of this drive division refers to that by drive division, the switch element of switch portion being carried out to conducting disconnects the action driving;

Driving power portion is supplied with electric power from switch portion, and is exported direct current power after the action of drive division starts;

Startup portion is supplied with electric power from DC power supply portion, and driving power portion is supplied with to electric power before the action of drive division starts;

Control power supply unit, from driving power portion, supplied with electric power, at the output voltage of driving power portion, be more than the reference voltage of regulation during, generate as the direct current power of the power supply of control part and be supplied to control part; And

Timing portion, this timing portion carries out timing to accumulative total service time, and this accumulative total is at least added up timing service time in the action of drive division, and is not reset;

As the operating frequency of the frequency of the action of above-mentioned drive division, corresponding to controlling, decide by the both end voltage of capacitor, this control makes both end voltage variation with capacitor corresponding to the output of control part;

Control part is when discharge lamp starts, after by each filament of discharge lamp, the preheating of preheating is moved respectively, the startup action that lighting a lamp of discharge lamp started, then makes the both end voltage of controlling with capacitor change, to transfer to the operating stably of lighting a lamp of sustain discharge lamp;

Drive division, after the output of the electric power from control power supply unit starts, does not start the action of drive division in the dwell time of regulation;

Control part is after reaching time device lifetime of regulation service time by the accumulative total of timing portion timing, and the Duration Ratio that makes to start action reaches short before the time device lifetime service time by the accumulative total of timing portion timing.

10. a ligthing paraphernalia, is characterized in that, possesses the discharge lamp ignition device described in any one in claim 1 to 9 and keeps the appliance body of discharge lamp ignition device.

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