CN101873755A - Discharge lamp ignition device, supply unit and ligthing paraphernalia - Google Patents

Abstract

The invention provides a kind of discharge lamp ignition device, supply unit and ligthing paraphernalia, can avoid after just starting, on circuit element or discharge lamp, acting on excessive electric stress.Possess DC power supply portion, with discharge lamp constitute resonant circuit resonant structure, switch the switch portion that is connected of DC power supply portion and resonant structure and by to make switch portion move from the drive division of resonant structure to discharge lamp output AC electric power corresponding to the frequency of controlling with the both end voltage of capacitor.Drive division does not begin action in the dwell time T1 of regulation after just starting, begin action after through dwell time T1.Owing in dwell time T1, can make control stable with the both end voltage of capacitor, so even the situation of behind the stopping of short time, restarting also can avoid after just starting circuit element or the excessive electric stress of discharge lamp effect.

Description

Discharge lamp ignition device, supply unit and ligthing paraphernalia

Technical field

The present invention relates to discharge lamp ignition device, supply unit and ligthing paraphernalia.

Background technology

In the past, a kind of discharge lamp ignition device is provided, possess output DC power DC power supply portion, constitute the resonant structure of resonant circuit, comprise 1 switch element and at least with discharge lamp along with the conducting of this switch element disconnects and switches the switch portion that is connected of DC power supply portion and resonant structure and disconnect by the switch element conducting with switch portion and to drive and from the drive division (for example with reference to patent documentation 1 and patent documentation 2) of resonant structure to discharge lamp supply alternating electromotive force.To the resonance frequency of the resonant circuit that the output power of discharge lamp can constitute by discharge lamp and resonant structure, the relation of the frequency (below be called " operating frequency ") of the action of switch portion conducting/disconnection is controlled with drive division.

In this discharge lamp ignition device, the control that possesses that has uses capacitor, drive division to constitute to move with the operating frequency of the both end voltage of capacitor corresponding to control.In this discharge lamp ignition device, use capacitor charging/discharging by controlling by the circuit of control usefulness, change the operating frequency of drive division, can control output power thus to discharge lamp.In addition, when the change of operating frequency, by the time constant of control with capacitor, operating frequency and gradually change to the output power of discharge lamp is so be difficult for the effect electric stress with making operating frequency and compare with the situation of stepped variation to the output power of discharge lamp on circuit element and discharge lamp.

But, in above-mentioned discharge lamp ignition device, the both end voltage that stops to control with capacitor the back in the short time waits because of discharging under the situation that does not have to restart when fully recovering, the output power of resonant structure temporarily exceedingly becomes big after just starting, and might act on excessive electric stress on circuit element and discharge lamp.

In addition, known in the past will from the direct voltage of DC power supply or from the AC voltage conversion of AC power for the direct voltage of hope size, and this direct voltage is transformed to high frequency voltage is supplied with action electric power to the load of discharge lamp etc. supply unit again.As the mapping device in such supply unit, use widely and can guarantee stable output voltage and can improve the DC power supply circuit that constitutes by the boost chopper electric current of the distortion of input current waveform large-scale input supply voltage to the direct voltage of hope size.

The elemental motion of DC power supply circuit generally is for example to disclose such action in the patent documentation 3, switch motion by switch element, carry out repeatedly to the savings of the energy of inductor and from the release of the savings energy of inductor, this is released energy supply with to the load circuit that comprises discharge lamp via diode and smoothing capacitor.Inductor is connected in the mode at the conducting of switch element time savings energy, detects the switching current that flows through this switch element, if this current value reaches setting, then controls, so that switch element is switched to disconnection.Above-mentioned switch element is switched to the setting of disconnection, decide by output voltage and this detection voltage of use error amplifier FEEDBACK CONTROL that detects boost chopper.In addition, the timing that switch element is switched to conducting decides by the timing that is detected inductor release savings energy by zero current detection portion.

In zero current detection portion, the secondary coiling is set in inductor, detect the timing that inductor discharges the savings energy by monitoring the voltage that in this secondary coiling, produces.Promptly, because the voltage that produces in secondary coiling is when the energy savings of inductor and the polarity inversion of when release, if so for example connect the secondary coiling so that it produces negative voltage when energy is put aside, then when energy discharges, be reversed to positive voltage immediately, after energy discharges, converge near the voltage about 0V.So,, can detect the exergonic timing of savings of inductor by monitoring near the voltage the 0V in the moment that positive voltage descends.

In addition, the output voltage of the input power supply of DC power supply circuit for example is 100V～200V, promptly the output voltage at the input power supply is under the high-tension situation, be controlled to be from the afore mentioned rules value of the electric current that flow through switch element of conducting when disconnecting the diverter switch element lowlyer, to be that the situation of 100V is compared conduction period of switch element shorter so that output voltage is situation and the output voltage of 200V.

On the other hand, in constituting the diode of DC power supply circuit, when when changing reverse blas into, because of the influence of the charge carrier put aside along bias voltage the time has the short time to the contrary recovery time of flowing through electric current against direction along bias voltage.Thereby, when disconnection switches to conducting, might from smoothing capacitor to switch element supply with bigger electric current during the contrary recovery time of this diode at switch element.

In boost chopper in the past, under the temporary low situation of output voltage of input power supply,, can not in inductor, put aside sufficient energy even switch element switches to conducting.But, because will flow through the afore mentioned rules value of the electric current of switch element as described above sets lowlyer, so, so under the inadequate state of savings of the energy of inductor, switch element is being switched to disconnection in the contrary recovery time of above-mentioned diode because the electric current flase drop that will flow through surveys to flowing through the switching current of switch element.So the energy of savings in inductor is insufficient, thus the energy of savings by abrupt release, the zero current detection portion that detects this situation switches to conducting with switch element.Therefore, if the unusual continuation of input power supply, then switch element sometimes with the very short cycle, particularly with conducting/disconnections repeatedly of nanosecond unit, might be because of switching losses increase switch element heat damage.

In addition, provided in the past and possessed by from the power supply supply capability of outside and the DC power supply portion of output DC power and with the direct current power proper transformation of DC power supply portion output and to the supply unit (for example with reference to patent documentation 4) of the power converter portion of load output.Load for example is a discharge lamp, and power converter portion for example is a converter circuit.

And then, in this supply unit, the unusual judging part of the load-side that has or not of unusual judging part of the mains side that has or not that possesses the abnormality of judging DC power supply portion that has and at least one side's who judges power converter portion and load abnormality.As abnormality by the unusual judgement section judges of mains side, the low state that the output voltage of DC power supply portion is for example arranged, as abnormality, for example there is load correctly not to be connected no-load condition in the power converter portion by the unusual judgement section judges of load-side.

The unusual judgement that the unusual judging part of mains side carries out, for example be situation about eliminating at short notice mostly because of to the temporary grade that lowly causes of the input electric power of DC power supply portion, so action when being unusual by the unusual judgement section judges of mains side, not that the output of power converter portion is stopped, reducing such action and preferably be made as the output power that temporarily makes power converter portion.

But, because power converter portion is located at the back level of DC power supply portion, so when being abnormality by the unusual judgement section judges of mains side, the situation that is judged as abnormality in the unusual judging part of load-side is more by mistake.And, make during for abnormality DC power supply portion and power converter portion stop action by the unusual judgement section judges of load-side if constitute, then, might not make the output power of power converter portion reduce such action in fact owing to stop because of erroneous judgement as described above is disconnected.

[patent documentation 1] TOHKEMY 2004-327116 communique

[patent documentation 2] TOHKEMY 2008-269860 communique

[patent documentation 3] TOHKEMY 2003-217883 communique

[patent documentation 4] TOHKEMY 2005-19172 communique

Summary of the invention

The present invention makes in view of above-mentioned reason, and its objective is provides a kind of discharge lamp ignition device and the ligthing paraphernalia that can avoid acting on excessive electric stress after just starting on circuit element or discharge lamp.

Another object of the present invention provides a kind of supply unit that switch element damages under the unusual situation that can prevent to have taken place in the output voltage of input power supply.

Another object of the present invention provides a kind of disconnected supply unit that stops that causing of erroneous judgement that can suppress abnormality.

According to the 1st mode of the present invention, it is characterized in that possessing: DC power supply portion, output DC power; Resonant structure constitutes resonant circuit with discharge lamp; Switch portion comprises 1 switch element at least, along with the conducting of this switch element disconnects and switches being connected of DC power supply portion and resonant structure; Drive division by the switch element of conducting disconnection driving switch portion, is supplied with alternating electromotive force from resonant structure to discharge lamp; Control part, the frequency of the action by controlling and driving portion, control is from the frequency of resonant structure to the alternating electromotive force of discharge lamp output; Driving power portion begins the back by from the switch portion supply capability in the action of drive division, output DC power; Startup portion, before the action of drive division begins by from DC power supply portion supply capability, to driving power portion supply capability; The control power supply unit, by from driving power portion supply capability, more than the output voltage of driving power portion is the reference voltage of regulation during in, generate direct current power as the power supply of control part, control part is supplied with; Make control that both end voltage changes both end voltage decision as the operating frequency of the frequency of drive division driving switch portion according to output with capacitor corresponding to control part; Control part is when the startup of discharge lamp, after each filament of discharge lamp is distinguished the preheating action of preheating, begin the startup of the lighting a lamp action of discharge lamp, control is changed, with the both end voltage of capacitor to transfer to the operating stably of lighting a lamp of keeping discharge lamp; Drive division does not make the action beginning in the dwell time of regulation after the output of beginning from the electric power of control power supply unit.

According to the 1st mode of the present invention, owing in dwell time, can make control stable with the both end voltage of capacitor, even so the situation of restarting behind the stopping of short time can avoid also that the output power of resonant structure after just starting is provisional exceedingly to be become big and constituting the excessive electric stress of effect on the circuit element of resonant structure or the discharge lamp.

According to the 2nd mode of the present invention, it is characterized in that, possess: DC power supply circuit, have at least 1 inductor and be connected in series in switch element on the inductor, by the conducting/disconnection of diverter switch element, carry out to the savings of the energy of inductor and from the release of the energy of inductor repeatedly, will be being transformed to direct voltage from the direct voltage of DC power supply or from the pulsating voltage behind the ac voltage rectifier of AC power; Load circuit is accepted the output voltage of DC power supply circuit, and action electric power is supplied with in load; The output voltage test section, the output voltage of detection DC power supply circuit; The DC power supply control circuit, the conducting/disconnection of the switch element by switching DC power supply circuit according to the testing result of output voltage test section and the output voltage of DC power supply circuit is controlled to be the voltage of the size of regulation; The DC power supply control circuit has: zero current detection portion becomes the predetermined electric current value with next output zero-signal if flow through the electric current of inductor; Peak current detection portion becomes more than the predetermined electric current value then exports peak signal if flow through the electric current of the switch element of DC power supply circuit; Drive division switches to the switch element of DC power supply circuit conducting and according to peak signal the switch element of DC power supply circuit is switched to disconnection according to zero-signal; Zero current detection portion possesses zero-signal after the electric current that will flow through inductor becomes below the predetermined electric current value and exports to the shielding part that the action of drive division stops specified time limit.

According to the 2nd mode of the present invention, provisional low and in inductor, can not put aside under the situation of sufficient energy at the output voltage of input power supply, can prevent that switch element moment of DC power supply circuit from switching to conducting.Thereby, even the output voltage at the input power supply has taken place under the unusual situation, the switch element that also can prevent DC power supply circuit is with the situation generation of very short cycle switched conductive/disconnections, can prevent the cause thermal damage of the switch element that the increase of switching losses causes.

According to the 3rd mode of the present invention, it is characterized in that possessing: DC power supply portion, by the power supply supply capability from the outside, output DC power; Power converter portion exports the direct current power proper transformation of DC power supply portion output to load; The unusual judging part of mains side is judged the having or not of abnormality of DC power supply portion; The unusual judging part of load-side is judged at least one the having or not of abnormality of power converter portion and load; Control part is according to the judgement of the judgement of the unusual judging part of mains side and the unusual judging part of load-side and control power converter portion at least; Control part makes the startup action of lacking than operating stably to the output power of load from power converter portion when starting, before the beginning operating stably; Control part carries out startup action once more lasting specified time limit when being abnormality by the unusual judgement section judges of mains side; When being abnormality, only, the output of power converter portion is stopped in that unusual judgement section judges is not under the situation of abnormality by mains side by the unusual judgement section judges of load-side.

According to the 3rd mode of the present invention, make action that the judgement of the abnormality of carrying out based on the unusual judging part of mains side begins startup action once more make action that power converter portion stops more preferably, so be difficult for taking place along with the unusual of DC power supply portion stopping of the power converter portion that being judged as abnormality and being caused by the unusual judging part mistake of load-side than the judgement of the abnormality of carrying out based on the unusual judging part of load-side.

Description of drawings

Fig. 1 is the key diagram of an example of the action of expression embodiments of the present invention 1, the time of Fig. 1 (a) expression control voltage changes, Fig. 1 (b) expression changed to the time of the input voltage that stops execution portion, the time of the output voltage of Fig. 1 (c) expression stopping execution portion changes, the time of the output voltage of Fig. 1 (d) order of representation control part changes, Fig. 1 (e) expression control changed with the time of the both end voltage of capacitor, and the time of Fig. 1 (f) expression operating frequency changes.

Fig. 2 is the circuit module figure of expression execution mode 1.

Fig. 3 is the startup portion of expression execution mode 1 and the circuit module figure of control power supply unit.

Fig. 4 is the key diagram of an example of the action of expression execution mode 1, the time of the output voltage of Fig. 4 (a) expression DC power supply portion changes, Fig. 4 (b) represents respectively the time of respectively detecting voltage and driving voltage after the driving voltage dividing potential drop is changed, the time of the grid voltage of the 1st switch element of Fig. 4 (c) expression startup portion changes, the time of Fig. 4 (d) expression control voltage changes, the time of the output voltage of Fig. 4 (e) expression stopping execution portion changes, and Fig. 4 (f) expression is from the time variation of drive division to the magnitude of voltage of the drive signal of a switch element output of switch portion.

Fig. 5 is oscillating portion, the drive division of expression execution mode 1 and stops the circuit module figure of execution portion.

Fig. 6 is the key diagram of action of the oscillating portion of expression execution mode 1, the vibration of Fig. 6 (a) expression oscillating portion changed with the time of the both end voltage of capacitor, the time of the output voltage of the comparator of Fig. 6 (b) expression oscillating portion changes, the time of the magnitude of voltage of Fig. 6 (c) expression the 1st rectangular signal changes, and the time of the magnitude of voltage of Fig. 6 (d) expression the 1st drive signal changes.

Fig. 7 is the circuit module figure of expression embodiments of the present invention 2.

Fig. 8 is the circuit module figure of expression embodiments of the present invention 3.

Fig. 9 is the circuit module figure of the major part of expression execution mode 3.

Figure 10 is the key diagram of an example of the action of expression execution mode 3, the time of Figure 10 (a) expression control voltage changes, the time that the output voltage of control part is regulated in Figure 10 (b) expression changes, the time of the output voltage of Figure 10 (c) order of representation control part changes, Figure 10 (d) expression control changed with the time of the both end voltage of capacitor, and the time of Figure 10 (f) expression operating frequency changes.

Figure 11 is the circuit module figure of major part of the comparative example of expression execution mode 3.

Figure 12 represents the example that changes with time of the input voltage of operational amplifier to the input of oscillating portion of execution mode 3, and Figure 12 (a) expression environment temperature is near the situation the normal temperature, and Figure 12 (b) expression environment temperature is the situation of low temperature.

Figure 13 is illustrated in the execution mode 3 to the key diagram of input with the relation of the input voltage of the non-counter-rotating input terminal of operational amplifier and lamp electric power.

Figure 14 is the key diagram that is illustrated in the relation of environment temperature and lamp current and lamp electric power in the execution mode 3.

Figure 15 is the circuit module figure of expression embodiments of the present invention 4.

Figure 16 is the key diagram of an example of the action of expression execution mode 4, the time of Figure 16 (a) expression control voltage changes, Figure 16 (b) expression changes to the time of the output voltage of drive division from stopping execution portion, the time of Figure 16 (c) expression report voltage changes, Figure 16 (d) expression changed from the time of drive division to the magnitude of voltage of the drive signal of a switch element output of switch portion, and the time of Figure 16 (e) expression clock frequency changes.

Figure 17 is the circuit module figure of expression embodiments of the present invention 5.

Figure 18 is the light a lamp key diagram of time and an example of the relation of light modulation ratio of the accumulative total of expression execution mode 5.

Figure 19 is the circuit module figure of expression embodiments of the present invention 6.

Figure 20 is the power supply test section of expression execution mode 6 and stops the circuit module figure of execution portion.

Figure 21 is the key diagram of an example of the action of expression execution mode 6, the time of the output voltage of Figure 21 (a) expression stopping control part changing, the time of the output voltage of Figure 21 (b) expression power supply test section changes, the time that Figure 21 (c) is illustrated in the output voltage that stops to be connected in the execution portion input comparator on the power supply test section changes, the time of the logic of Figure 21 (d) expression stopping execution portion and the output voltage of circuit changes, Figure 21 (e) expression postpones to change with the time of the both end voltage of capacitor, and the time of Figure 21 (f) expression report voltage changes.

Figure 22 is the power supply test section of expression execution mode 6 and the circuit module figure that stops the modification of execution portion.

Figure 23 is the circuit module figure of expression embodiments of the present invention 7.

Figure 24 is the circuit module figure of expression embodiments of the present invention 8.

Figure 25 is the circuit module figure of the major part of expression execution mode 8.

Figure 26 is the circuit module figure of expression embodiments of the present invention 9.

Figure 27 is the circuit diagram of the low test section of direct voltage of expression execution mode 9.

Figure 28 is the key diagram that does not reach duration of being illustrated in the low state of direct voltage in the execution mode 9 action under the situation of the time of restarting, the time of the output voltage of Figure 28 (a) expression DC power supply test section changes, the time of the output voltage of the comparator of the low judging part of Figure 28 (b) expression direct voltage changes, the time of the output voltage of the low judging part of Figure 28 (c) expression direct voltage changes, the time of the output voltage of Figure 28 (d) order of representation control part changes, the time of Figure 28 (e) expression operating frequency changes, and Figure 28 (f) expression stopping control part changing to the time that drives the output voltage of using integrated circuit.

Figure 29 is the key diagram that does not reach duration of being illustrated in the low state of direct voltage in the execution mode 9 action under the situation of the time of restarting, the time of the output voltage of Figure 29 (a) expression DC power supply test section changes, the time of the output voltage of the comparator of the low judging part of Figure 29 (b) expression direct voltage changes, the time of the output voltage of the low judging part of Figure 29 (c) expression direct voltage changes, the time of the output voltage of Figure 29 (d) order of representation control part changes, the time of Figure 29 (e) expression operating frequency changes, and Figure 29 (f) expression stopping control part changing to the time that drives the output voltage of using integrated circuit.

Figure 30 is the circuit module figure of the major part of expression embodiments of the present invention 10.

Figure 31 is the key diagram of action of the zero current detection portion of expression execution mode 10, the time of the output voltage of Figure 31 (a) expression power drives portion changes, Figure 31 (b) expression changed to the time of the input voltage of zero current detection portion, Figure 31 (c) changes time of output voltage of the input comparator of expression zero current detection portion, the reservation of Figure 31 (d) expression zero current detection portion changed with the time of the both end voltage of capacitor, the time of the output voltage of Figure 31 (e) expression single-shot trigger circuit changes, the time of the output voltage of the output comparator of Figure 31 (f) expression zero current detection portion changes, and the time of the output voltage of Figure 31 (g) expression zero current detection portion changes.

Figure 32 is the circuit module figure of expression execution mode 10.

Figure 33 is the circuit module figure of the major part of expression embodiments of the present invention 11.

Figure 34 is the key diagram of the action of expression execution mode 11, and the time of the output voltage of Figure 34 (a) expression report portion changes, and Figure 34 (b) expression changed from the time of resonant structure to the output voltage of discharge lamp, and the time of Figure 34 (c) expression operating frequency changes.

Figure 35 is the circuit module figure of expression embodiments of the present invention 12.

Figure 36 is the circuit module figure of the major part of expression execution mode 12.

Figure 37 is the circuit module figure of major part of the modification of expression execution mode 12.

Figure 38 is the key diagram of the example of the configuration on the printed wiring board of the expression circuit element that constitutes execution mode 12.

Figure 39 is the key diagram of the comparative example of expression execution mode 12.

Figure 40 (a)～Figure 40 (c) represents respectively execution mode 12 is accommodated in state in the housing, and Figure 40 (a) is a vertical view, and Figure 40 (b) is a front view, and Figure 40 (c) is a right side view.

Figure 41 is the stereogram of the example of the expression ligthing paraphernalia that uses execution mode 12.

Figure 42 is another routine stereogram that the ligthing paraphernalia of execution mode 12 is used in expression.

Figure 43 is the circuit diagram of the execution mode 13 of the relevant supply unit of the present invention of expression.

Figure 44 is the circuit diagram of startup portion, control power supply comparing section and the 1st control power supply generating unit of expression execution mode 13.

Figure 45 (a)～Figure 45 (g) is the time diagram of action that is used for illustrating the control circuit of execution mode 13.

Figure 46 is the circuit diagram of the converter control circuit of expression execution mode 13.

Figure 47 (a)～Figure 47 (g) is the time diagram that is used for illustrating the sequential control of execution mode 13.

Figure 48 is the circuit diagram that stops execution portion of expression execution mode 13.

Figure 49 is the flow chart of elemental motion that is used for illustrating the action initialization circuit of execution mode 13.

Figure 50 is the circuit diagram of the zero current detection portion of expression execution mode 13.

Figure 51 (a)～Figure 51 (f) is the time diagram of action that is used for illustrating the zero current detection portion of execution mode 13.

Figure 52 is the circuit diagram of expression about the zero current detection portion of the execution mode 14 of supply unit of the present invention.

Figure 53 is the circuit diagram of the filter section of expression execution mode 14.

Figure 54 (a)～Figure 54 (e) is the time diagram of action that is used for illustrating the zero current detection portion of execution mode 14.

Figure 55 is the circuit diagram of the execution mode 15 of the relevant supply unit of the present invention of expression.

Figure 56 is the circuit diagram of the low judging part of voltage of expression execution mode 15.

Figure 57 (a)～Figure 57 (f) is the time diagram that is used for illustrating the action of the low judging part of voltage under the temporary low situation of the output voltage of execution mode 15.

Figure 58 (a)～Figure 58 (f) is the time diagram that is used for illustrating the action of the low judging part of voltage under the low situation of the output voltage continuation of execution mode 15.

Figure 59 is the flow chart that is used for illustrating the unusual judgment processing of execution mode 15.

Figure 60 is the circuit diagram of the execution mode 16 of the relevant supply unit of the present invention of expression.

Figure 61 is the circuit diagram of the voltage rising judging part of expression execution mode 16.

Figure 62 (a)～Figure 62 (d) is used for illustrating the voltage rising judging part of execution mode 16 and the time diagram that begins the action of portion again.

Figure 63 is the circuit module figure of expression embodiments of the present invention 17.

Figure 64 is the key diagram of an example of the action of expression execution mode 17, the time of Figure 64 (a) expression control voltage changes, Figure 64 (b) expression changed to the time of the input voltage that stops execution portion, the time of the output voltage of Figure 64 (c) expression stopping execution portion changes, the time of the output voltage of Figure 64 (d) order of representation control part changes, Figure 64 (e) expression control changed with the time of the both end voltage of capacitor, the time of Figure 64 (f) expression operating frequency changes, and the time of Figure 64 (g) expression clock frequency changes.

Figure 65 is the circuit module figure of major part of the modification of expression execution mode 17.

Figure 66 is the module map of expression embodiments of the present invention 18.

Figure 67 is the key diagram of an example of the action of expression execution mode 18, the time of Figure 67 (a) expression control voltage changes, the time of the output voltage of Figure 67 (b) expression stopping control part changing, the time of the output voltage of Figure 67 (c) expression stopping execution portion changes, the time of the output voltage of Figure 67 (d) order of representation control part changes, Figure 67 (e) expression control changed with the time of the both end voltage of capacitor, and the time of Figure 67 (f) expression operating frequency changes.

Figure 68 is the circuit module figure of expression embodiments of the present invention 19.

Embodiment

Below, of the present inventionly preferred embodiment describe being used for implementing with reference to accompanying drawing.

(execution mode 1)

Present embodiment as shown in Figure 2, it is the device that the discharge lamp La of the general hot cathode type with a pair of filament (not shown) is lit a lamp, possess: rectification part DB is made of the alternating electromotive force full-wave rectification that will import from the AC power AC of outside known diode bridge; DC power supply portion 1 is with the output of rectification part DB smoothing and output DC power at least; Switch portion 21 possesses the series circuit of two switch element Q10, Q20 between the output that is connected DC power supply portion 1, with the two ends of the switch element Q20 of low voltage side (downside) as output; And resonant structure 22, being connected between the output of switch portion 21, La constitutes resonant circuit with discharge lamp.That is, switch portion 21 and resonant structure 22 constitute the converter circuit of so-called semi-bridge type as a whole.In addition, the output head grounding of the low voltage side of DC power supply portion 1.

DC power supply portion 1 for example can be made of the smmothing capacitor between the output that is connected rectification part DB (not shown), and in the case, the two ends of smmothing capacitor become the output of DC power supply portion 1.

In addition, resonant structure 22 possesses on the tie point of switch element Q10, Q20 that an end is connected switch portion 21 and the other end is connected the capacitor C2 on the discharge lamp La via the capacitor C1 of discharge lamp La ground connection with series circuit and (promptly between the filament of discharge lamp La) in parallel of inductor L1.

And then present embodiment possesses the preheating part 23 that is used for when the startup of discharge lamp La each filament of discharge lamp La being distinguished preheating.Preheating part 23 possess have an end be connected on the tie point of switch element Q10, Q20 of switch portion 21 via capacitor C3 and the once coiling of other end ground connection and separately and the series circuit of capacitor C4, C5 be connected the transformer Tr1 of two secondaries coilings between the two ends of each filament of discharge lamp La.

In addition, present embodiment possesses: drive division 31, be connected on each switch element Q10, Q20 of switch portion 21 via resistance R 1, R2 respectively, disconnect each switch element Q10, Q20 of driving switch portion 21 and supply with alternating electromotive force from 22 couples of discharge lamp La of resonant structure by conducting; And sequential control portion 41, the frequency of the action by controlling and driving portion 31 is controlled from the frequency of the alternating electromotive force of 22 pairs of discharge lamp La outputs of resonant structure.

Drive division 31 is located at the driving that is made of high-withstand-voltage integrated circuit (HVIC) and uses in the integrated circuit 3, and sequential control portion 41 is located at the control that is made of the integrated circuit that is called microcontroller (microcomputer) and uses in the integrated circuit 4.With integrated circuit 4, only is 2 grade and do not comprise the structure of A/D converter and D/A converter if use the magnitude of voltage of input and output as control, then can suppress lessly with the consumption electric power in the integrated circuit 4 control.

In addition, present embodiment possesses the driving power portion 5 of the direct current power of the power supply of being used integrated circuit 3 after the action of drive division 31 begins from switch portion 21 supply capabilities, output as driving.Driving power portion 5 possesses plus earth, and negative electrode is via the outlet side diode of the parallel circuits ground connection of outlet side capacitor C101 and Zener diode ZD1 and negative electrode is connected via the input side capacitor on the connecting portion that input side diode on the tie point of switch element Q10, Q20 of switch portion 21 and anode be connected this input side diode and input side capacitor, and the both end voltage that makes outlet side capacitor C101 is an output voltage.Under the action from drive division 31 began both end voltage stable status through adequate time and outlet side capacitor C101, the both end voltage of outlet side capacitor C101 was that the output voltage of driving power portion 5 for example becomes 10V.

And then, driving with in the integrated circuit 3, be respectively equipped with the action of drive division 31 begins before and exported as the startup portion 32 of the direct current power of the power supply of driving power portion 5 from DC power supply portion 1 supply capability and generated during from driving power portion 5 supply capabilities and more than the output voltage of driving power portion 5 is the reference voltage of regulation as control with the control voltage vcc 1 (for example 5V) of the regulation of the power supply of integrated circuit 4 and control is used the control power supply unit 33 of integrated circuit 4 supplies.

If describe in detail, then as shown in Figure 3, startup portion 32 has the impedance component Z1 on the output that an end is connected on the output of high-voltage side of DC power supply portion 1, the other end is connected driving power portion 5 via the 1st switch element Q101.Promptly, in during the 1st switch element Q101 conducting of startup portion 32, the output voltage V dc of DC power supply portion 1 is outputed in the driving power portion 5 via impedance component Z1 and the 1st switch element Q101, and the outlet side capacitor C101 with driving power portion 5 charges thus.Above-mentioned the 1st switch element Q101 is made of the high withstand voltage field-effect transistor of n type raceway groove, the grid of the 1st switch element Q101 is connected on the tie point of DC power supply portion 1 and impedance component Z1 via resistance R 101, and the parallel circuits ground connection of the 2nd switch element Q102 that constitutes via the series circuit of diode D101 and Zener diode ZD2 and field-effect transistor by n type raceway groove.In addition, startup portion 32 has respectively 4 divider resistances with the output voltage of driving power portion 5 (below be called " driving voltage ") Vcc2 dividing potential drop, from the tie point of these divider resistances respectively different 3 kinds of output voltage (voltage ratio) detect voltage Va, Vb, Vc.And then startup portion 32 possesses in counter-rotating and is transfused to comparator C P1 on the 1st reference voltage Vr1 of regulation and lead-out terminal is connected the 2nd switch element Q102 via logic and circuit OR1 the grid in the input terminal.In the non-counter-rotating input terminal of comparator C P1, be transfused to detection voltage Vb, Vc via the multiplexer TG1 that uses transmission gate circuit to constitute.Above-mentioned multiplexer TG1 is connected on the lead-out terminal of comparator C P1, constitute, in during the output H of comparator C P1 (height) level the 2nd low detection voltage (below be called " the 2nd detects voltage ") Vb is input in the non-counter-rotating input terminal of comparator C P1, minimum detection voltage (below be called " the 3rd detection voltage ") Vc is input in the non-counter-rotating input terminal of comparator C P1 in during the output L of comparator C P1 (low) level.

Use Fig. 4 that the action of startup portion 32 is described.After power supply just is switched on, the output of comparator C P1 is the L level, inject terminal input the 3rd in the non-counter-rotating of comparator C P1 thus and detect voltage Vc, and by the 2nd switch element Q102 is disconnected, by the Zener voltage of Zener diode ZD2 with the 1st switch element Q101 conducting.During the 1st switch element Q101 conducting, the outlet side capacitor C101 of driving power portion 5 is recharged by the output power that impedance component Z1 and the 1st switch element Q101 via startup portion 32 are supplied to DC power supply portion 1, and both end voltage (driving voltage) Vcc2 is risen.Reach the 1st reference voltage Vr1 if the final the 3rd detects voltage Vc, then the output of comparator C P1 becomes the H level.So, input voltage to non-counter-rotating input terminal is changed to the 2nd detection voltage Vb higher than the 3rd detection voltage Vc, and, stop the supply to the electric power of driving power portion 5 from startup portion 32 by the 2nd switch element Q102 conducting is disconnected the 1st switch element Q101.Also do not begin action at this moment drive division 31,21 pairs of driving power portions 5 do not have supply capability from switch portion, so pass through the discharge of outlet side capacitor C101, driving voltage Vcc2 begins to descend.Reach the 1st reference voltage Vr1 if the final the 2nd detects voltage Vb, then the output of comparator C P1 becomes the L level once more, the output voltage of driving power portion 5 begins to rise, if then the 3rd detection voltage Vc reaches the 1st reference voltage Vr1, then the output of comparator C P1 becomes the H level once more.Then, supply with such direct current power shown in Fig. 4 (a) from DC power supply portion 1, and shown in Fig. 4 (e) from stop execution portion 34 (aftermentioned) to the input L level of logic and circuit OR1 and drive division 31 stop during, repetition by above-mentioned action, the grid voltage of the 1st switch element Q101 changes shown in Fig. 4 (c) like that, and driving voltage Vcc2 detects voltage Vc the 3rd like that shown in Fig. 4 (b) be the such upper voltage limit of the 1st reference voltage Vr1, and the 2nd detect voltage Vb and change up and down repeatedly between the such lower voltage limit of the 1st reference voltage Vr1.

Here, driving, be provided with the execution portion 34 that stops of controlling and driving portion 31 and startup portion 32 respectively with in the integrated circuit 3.The output that stops execution portion 34 is imported among logic and the circuit OR1, in during stopping the output L level of execution portion 34 drive division 31 stopped and will supply with conducting to the electric power of driving power portion 5 from startup portion 32, in during stopping the output H level of execution portion 34, by irrelevant with the output of comparator C P1 and with the 2nd switch element Q102 conducting, the 1st switch element Q101 is disconnected, will supply with to the electric power of driving power portion 5 from startup portion 32 and disconnect.Wherein, during stopping the output H level of execution portion 34 in, move (promptly generating the output of the driving usefulness of switch element Q10, Q20 such shown in Fig. 4 (f)) by drive division 31, carry out supplying with to the electric power of driving power portion 5 from switch portion 21.

In addition, control power supply unit 33 possesses detection voltage the highest in the detection voltage that the divider resistance that is transfused to startup portion 32 in non-counter-rotating input terminal exports (below be called " the 1st detects voltage ") Va and be transfused to the comparator C P2 of the 1st reference voltage Vr1 in the counter-rotating input terminal, be connected the series circuit of the output of driving power portion 5 and constant current circuit Ir1 between the earthing potential and Zener diode ZD3, base stage is connected on the tie point of constant current circuit Ir1 and Zener diode ZD3 and collector electrode is connected on the output of driving power portion 5, emitter is connected the transistor Q103 of control with the npn type on the integrated circuit 4 as the output of control power supply unit 33, and be connected in that the field-effect transistor by n type raceway groove on the Zener diode ZD3 constitutes in parallel and grid is connected switch element Q104 on the lead-out terminal of comparator C P2.Promptly, shown in Fig. 4 (d), control voltage vccs 1 to control with integrated circuit 4 outputs in constituting only during the 1st detection voltage Va is above the 1st reference voltage Vr1, the 1st detect voltage Va be lower than the 1st reference voltage Vr1 during in do not export control voltage vcc 1 (output voltage of promptly controlling power supply unit 33 is roughly 0), the driving voltage that the 1st detects voltage Va when being the 1st reference voltage Vr1 is a said reference voltage.Here, from driving the capacitor C51 ground connection of using via noise removing with the circuit of integrated circuit 4 output control voltage vccs 1 with 3 pairs of controls of integrated circuit.

In addition, driving with in the integrated circuit 3, be provided with the oscillating portion 35 of the output square wave corresponding with the frequency of the output of sequential control portion 41, drive division 31 disconnects switch element Q10, the Q20 of driving switch portion 21 with the frequency conducting of the output of oscillating portion 35.

Oscillating portion 35 as shown in Figure 5, possess by non-counter-rotating input terminal be connected in the sequential control portion 41 via resistance R 103 and via the parallel circuits ground connection of resistance R 104 and control electricity consumption container C 103 input terminal that reverses be connected that operational amplifier on the lead-out terminal constitutes and lead-out terminal via the voltage follower OP1 of two resistance R 106, R102 ground connection and in non-counter-rotating input terminal, be transfused to the 2nd reference voltage Vr2 of regulation and the input terminal that reverses is connected the control operational amplifier OP2 on the lead-out terminal of voltage follower OP1 via resistance R 106.The lead-out terminal of this operational amplifier OP2 is connected on the grid of charging with switch element Qc, this charging is connected in the charging that is transfused to report voltage vcc 3 in each input respectively with between output of current mirroring circuit CM1 and the resistance R 102 with switch element Qc, above-mentioned charging with another output of current mirroring circuit CM1 via vibration electricity consumption container C 102 ground connection.In addition, oscillating portion 35 possesses in an input and to be connected the 1st discharge that charging constitutes with the field-effect transistor by p type raceway groove on the above-mentioned output of current mirroring circuit CM1 via grid and to be transfused to switch element Qd and to report voltage vcc 3 and connecting the discharge current mirroring circuit CM2 that the electricity consumption container C 102 of vibrating, each output are distinguished ground connection on another input.And then oscillating portion 35 possesses a side the comparator C P3 that the counter-rotating input terminal is connected on the vibration electricity consumption container C 102 and is transfused to the 4th reference voltage Vr4 of the low regulation of the 3rd reference voltage Vr3 of regulation and Bi Di 3 reference voltage Vr3 via the multiplexer TG2 that uses transmission gate circuit to constitute in non-counter-rotating input terminal.The lead-out terminal that on above-mentioned multiplexer TG2, is connecting comparator C P3, in during the output H level that constitutes at comparator C P3 the 3rd reference voltage Vr3 is input in the non-counter-rotating input terminal of comparator C P3, the 4th reference voltage Vr4 is input in the non-counter-rotating input terminal of comparator C P3 in during the output L of comparator C P3 level.In addition, use on the current mirroring circuit CM2 in discharge, the 2nd discharge switch element Q105 that is being connected in parallel, the 2nd discharge is made of the field-effect transistor of n type raceway groove with switch element Q105, and grid is connected on the lead-out terminal of comparator C P3.

Action to oscillating portion 35 describes.Do not have under the fully charged state in vibration electricity consumption container C 102, comparator C P3 is output as the H level, thus, is transfused to the 3rd reference voltage Vr3 in the non-counter-rotating input terminal of comparator C P3, with switch element Q105 conducting.During this period, use the conducting of switch element Q105 with the 2nd discharge on the current mirroring circuit CM2 by being connected in discharge in parallel, be suppressed via the discharge of discharge with the vibration electricity consumption container C 102 of current mirroring circuit CM2, by use the charging of current mirroring circuit CM1 via charging, the both end voltage of vibration electricity consumption container C 102 rises gradually.The both end voltage of electricity consumption container C 102 reaches the 3rd reference voltage Vr3 if finally vibrate, then the output of comparator C P3 becomes the L level, input voltage to the non-counter-rotating input terminal of comparator C P3 becomes the 4th reference voltage Vr4, and the 2nd discharge is disconnected with switch element Q105.So, becoming than many with the charging current of current mirroring circuit CM1 via the discharging current of discharge via charging with current mirroring circuit CM2, the both end voltage of the electricity consumption container C 102 of vibrating thus descends gradually.And if the both end voltage of vibration electricity consumption container C 102 reaches the 4th reference voltage Vr4, then the output of comparator C P3 becomes the H level once more, below repeats same action.Thus, the both end voltage of vibration electricity consumption container C 102 promptly changes up and down between the 3rd reference voltage Vr3 and the 4th reference voltage Vr4 shown in Fig. 6 (a) like that repeatedly to the input voltage of the counter-rotating input terminal of comparator C P3, and the output of comparator C P3 becomes such square wave shown in Fig. 6 (b) .And then oscillating portion 35 has the output Shaping circuit 35a that the output Shaping of comparator C P3 is exported to drive division 31. output Shaping circuit 35a have shown in Fig. 6 (c) like that the 1st rectangular signal generating unit (not shown) that generates the 1st rectangular signal by the output of comparator C P3 being carried out two divided-frequency for example, generation is with the 2nd rectangular signal generating unit (not shown) of the 2nd rectangular signal of the output counter-rotating of the 1st rectangular signal, and td dead time of the constant time lag of the ON (conducting) (counter-rotating from the L level to the H level) by making the 1st rectangular signal regulation generates shown in Fig. 6 (d) the such the 1st timing that drives signal and the ON (conducting) by making the 2nd rectangular signal and above-mentioned same delay and generates the 2nd and drive signal and drive signal and the 2nd with the 1st and drive signal and output to respectively generating unit dead time (not shown) the drive division 31. Drive division 31 has a switch element Q10 of switch portion of making 21 conducting and at (L level during) the 1st drive division 31a that breaks and another switch element Q20 that makes switch portion 21 during the OFF of the 1st drive signal (disconnection) conducting and the 2nd drive division 31b that breaks in the conduction period of the 2nd drive signal in conduction period of the 1st drive signal (H level during) during the OFF of the 2nd drive signal (disconnection) .That is, by above-mentioned dead time of generating unit, two switch element Q10, Q20 preventing switch portion 21 are by the while conducting.In said structure, do not require extra high capability value for vibration electricity consumption container C 102, so vibration electricity consumption container C 102 can be in control with constituting in the integrated circuit 4.

Here, the charging current and the discharging current of vibration electricity consumption container C 102 are respectively: high more with the input voltage of the counter-rotating input terminal of operational amplifier OP2 to control, promptly to control the both end voltage of electricity consumption container C 103 high more then more little.That is, the frequency of above-mentioned the 1st drive signal and the 2nd drive signal, be drive division 31 action frequency and to the frequency of the alternating electromotive force of discharge lamp La output (below be called " operating frequency) be: the both end voltage of control electricity consumption container C 103 is high more then low more.

Control the time of sequential control portion 41 by beginning according to the supply shown in Fig. 1 (a) from control voltage vcc 1 with integrated circuit 4, the both end voltage of the control electricity consumption container C 103 shown in Fig. 1 (e) is changed, thus after the preheating action t1～t2 that each filament of discharge lamp La is distinguished preheating, make the startup action t2～t3 of the beginning of lighting a lamp of discharge lamp La, transfer to the operating stably t3～t4 that lights a lamp that keeps discharge lamp La then.For example, sequential control portion 41 is via the unit of pwm signal such shown in 103 pairs of control of resistance R electricity consumption container C, 103 output maps 1 (d), makes the both end voltage variation of control electricity consumption container C 103 by the duty ratio of this pwm signal.Particularly, by in preheating action t1～t2, making the said PWM signal stop (in other words making above-mentioned duty ratio is 0), in operating stably t3～t4, improving above-mentioned duty ratio than starting action t2～t3, the both end voltage stage ground of control electricity consumption container C 103 is risen, promptly shown in Fig. 1 (f), make the interim decline of operating frequency f1～f3.That is, making operating frequency be the highest operating frequency f1 in t1～t2 is moved in preheating, is than the low operating frequency f2 of preheating action t1～t2 in starting action t2～t3, is than starting lower operating frequency f3 among action t2～t3 in operating stably t3～t4.In addition, the output of sequential control portion 41 is not limited to pwm signal, so long as the signal that the both end voltage of control electricity consumption container C 103 is changed is just passable.Make the resonance frequency height of operating frequency f1～f3 than the resonant circuit of discharge lamp La and resonant structure 22 formations, promptly operating frequency f1～f3 is low more, from the electric power increase more of 22 pairs of discharge lamp La outputs of resonant structure.That is, by the stage decline of operating frequency f1 as described above～f3, to the interim increase of the output power of discharge lamp La.In addition, the timing t 3 that begins to start the timing t 2 of action t2～t3 and beginning operating stably t3～t4 is roughly necessarily the duration of preheating action t1～t2 and the duration that starts action t2～t3 respectively respectively for example by the timing decision.

And then present embodiment has and judges whether to making the unusual judging part 61 of the abnormality that drive division 31 stops.In the example of Fig. 2, unusual judging part 61 integral body are located at the outside of control with integrated circuit 4, but also can with the part of circuit element that constitutes unusual judging part 61 integrated to control with in the integrated circuit 4.In addition, in control with in the integrated circuit 4, be provided with when unusual judging part 61 be judged as be in the time of should making the state that drive division 31 stops driving being indicated stopping of drive division 31 at least with the execution portion 34 that stops of integrated circuit 3 and makes that sequential control portion 41 stops stopping control part 42.Stop control part 42 and constitute control part in the technical scheme with sequential control portion 41.Be connected via resistance 51 on the circuit of control voltage vcc 1 to the circuit that stops execution portion 34 that drives with integrated circuit 3 from the control part 42 that stops of control with integrated circuit 4.Stop control part 42 and usually the current potentials of foregoing circuit are made as the L level that equates with earthing potential, when drive division 31 is stopped, being made as and controlling the H level that voltage vcc 1 equates and indicate stopping of drive division 31 by current potential with foregoing circuit.That is, be instructed to drive division 31 stop during in above-mentioned resistance R 51, do not flow through electric current and do not consume electric power, with make in above-mentioned resistance R 51, always flow through electric current structure mutually specific consumption electric power reduce.In Fig. 1, in timing shown in Figure 4, the output (promptly stopping the input of execution portion 34) that stops control part 42 becomes the H level, and the output that stops execution portion 34 thus becomes the L level, and the action of oscillating portion 35 and drive division 31 is stopped respectively.

Be judged as the state of abnormality as unusual judging part 61, can consider on resonant structure 22, not connect the no-load condition of discharge lamp La.Unusual judging part 61 like this can be realized by technique known, so diagram and detailed explanation are omitted.

Here, in operating stably t3～t4, power supply is disconnected under at once that power turn-on is such then situation, in the moment with power turn-on, if the discharge of control electricity consumption container C 103 is insufficient, then the output power of resonant structure 22 is temporary after the firm conducting of power supply as described above exceedingly becomes big, the excessive electric stress of effect on circuit element that constitutes resonant structure 22 or discharge lamp La.

So, in the present embodiment, stopped execution portion 34 before the output from control voltage vcc 1 begins through the dwell time T1 that stipulates, output is made as the L level and drive division 31 is stopped, after through dwell time T1, output is made as the H level and begins the action of drive division 31.This dwell time T1 is made as the time of the discharge of enough control electricity consumption container C 103.Thereby, even in operating stably t3～t4, power supply is disconnected at once that power turn-on is such afterwards situation as described above, owing to when starting, in dwell time T1, carried out the discharge of control electricity consumption container C 103, so also can avoid the excessive electric stress of effect on the circuit element of resonant structure 22 and discharge lamp La.

In addition, in the example of Fig. 1, when beginning to play the end of operating stably t3～t4 till the t4 by output from control voltage vcc 1, to be maintained the L level to the input that stops execution portion 34 (promptly stopping the output of control part 42), after beginning through dwell time T1, the output from control voltage vcc 1 begins preheating action t1～t2 thus, but after the output of control voltage vcc 1 begins, become under the situation that the H level is changed to the L level then, beginning preheating after through dwell time T1 and move t1～t2 from become the L level to the input that stops implementation portion 34 to the input that stops execution portion 34.Promptly, strictly say, from control power supply unit 33 output control voltage vccs 1 and to the input that stops execution portion 34 be the L level state continuance moment of dwell time T1 begin preheating action t1～t2, finish from operating stably t3～t4 to then begin preheating action t1～t2 during guaranteed stopping of dwell time T1 at least.

In addition, in the stopping of drive division 31, nonsensical to the output of oscillating portion 35 from sequential control portion 41.So, sequential control portion 41 also can by and stop the transmitting-receiving or the timing of the signal of telecommunication between the execution portion 34, in the stopping of drive division 31, do not generate the signal of telecommunication (in above-mentioned example, being pwm signal) to oscillating portion 35 inputs.If adopt this structure, then can realize the minimizing of the consumption electric power in the stopping of drive division 31, relaxed requirement for the durability of the circuit element of startup portion 32 etc. thereupon, can realize driving miniaturization thus with integrated circuit 3.

(execution mode 2)

The basic structure of present embodiment and execution mode 1 are common, so give identical label and omit explanation for common part.

Present embodiment possesses the transducer 62 of the human body of being used for and judges the human body judging part 43a that has or not the existence of human body in the detection range of stipulating according to the output of this transducer 62 as shown in Figure 7.That is, constitute so-called human body sensor by transducer 62 and human body judging part 43a.Human body judging part 43a is located at control with in the integrated circuit 4, and transducer 62 and human body judging part 43a will control voltage vcc 1 as power supply.As transducer 62, for example can use the thermoelectric pickup of detection, because transducer 62 and human body judging part 43a can both realize by known technology, so detailed diagram and explanation are omitted from the hot line (infrared light) of human body radiation.

In the present embodiment, sequential control portion 41 begins lighting a lamp of discharge lamp La by a series of action from the preheating action when having judged existing of human body by human body judging part 43a.In addition, rise in the existence that is not determined human body by human body judging part 43a and to have passed through the lighting a lamp during the retention time of regulation, stop control part 42 by output being made as the H level and the output of sequential control portion 41 being stopped, La turns off the light with discharge lamp.

According to said structure, can suppress to forget the meaningless power consumption that operation that discharge lamp La is turned off the light causes because of the user.

(execution mode 3)

The basic structure of present embodiment and execution mode 1 are common, so give identical label and omit explanation for common part.

Present embodiment as shown in Figure 8, possess the known lightness transducer 63 of detection by the lightness in the space of discharge lamp La illumination, with in the integrated circuit 4, be provided with the adjusting control part 44 that in the operating stably of sequential control portion 41, generates the output corresponding at least in control with the output of lightness transducer 63.As shown in Figure 9, regulate control part 44 and be connected on the control electricity consumption container C 103, change by the both end voltage that makes control electricity consumption container C 103 equally with sequential control portion 41 and come the control action frequency via resistance.In the present embodiment, regulate control part 44 and sequential control portion 41 same output pwm signals, but also pwm signal not necessarily of the output of regulating control part 44, so long as make the signal of two ends variation of control electricity consumption container C 103 just passable.

In addition, switch portion 21 has the detection resistance R3 that is connected between switch element Q20 and the earthing potential in order to detect the electric current among the switch element Q20 that flows through low voltage side (downside).

And then, in the oscillating portion 35 that drives with integrated circuit 3, impose variation, so that it regulates operating frequency according to the current value that flows through detection resistance R3 (being the current potential of the tie point of switch element Q20 and detection resistance R3), the output of sequential control portion 41 and the output of adjusting control part 44.That is, by sequential control portion 41, stop control part 42 and regulate control part 44 constituting control part in the technical scheme.

If explain, then in oscillating portion 35, replace voltage follower OP1 and be provided with input operational amplifier OP3.This input is transfused to the both end voltage of control electricity consumption container C 103 in non-counter-rotating input terminal with operational amplifier OP3, and in the counter-rotating input terminal, be transfused to the detection resistance R3 of switch portion 21 and the voltage of the tie point of switch element Q20 (below be called " current detection voltage "), and lead-out terminal is connected via capacitor C104 with the input terminal that reverses and constitutes integrating circuit via resistance R 109.Input, is connected control and uses on the counter-rotating input terminal of operational amplifier OP2 via resistance R 110 and make negative electrode towards the diode D102 of input with operational amplifier OP3 side with the lead-out terminal of operational amplifier OP3.That is, the high more then input of integrated value of the both end voltage of control electricity consumption container C 103 and the difference of current detection voltage is high more with the output voltage of operational amplifier OP3, controls the output voltage step-down with operational amplifier OP2 thus, the operating frequency step-down.Sequential control portion 41 is connected on the control electricity consumption container C 103 via resistance R 103 equally with execution mode 1, regulates control part 44 and also is connected on the control electricity consumption container C 103 via other resistance R 31.

Utilize Figure 10 that the action of present embodiment is described.If the supply of the control voltage vcc 1 shown in beginning Figure 10 (a) then, is being regulated control part 44 and is at first being begun action after the short stipulated time than dwell time T1.The output of the adjusting control part 44 shown in Figure 10 (b) is from the action that begins to regulate control part 44 to the end that starts action t2～t3 the time till the t3, irrelevant and duty ratio is made as 1 with the output of lightness transducer 63, t3～t4 is made as corresponding to the duty ratio by the 63 detected lightnesses of lightness transducer in operating stably.The output of the sequential control portion 41 shown in Figure 10 (c) was made as 0 with duty ratio before the zero hour that starts action t2～t3, t2～t3 is made as duty ratio than 1 little and be not 0 value in starting action, and t3～t4 is made as 1 with duty ratio in operating stably.T2 when starting the beginning of action t2～t3, the both end voltage of the control electricity consumption container C 103 shown in Figure 10 (d) rises by the output of sequential control portion 41, and the operating frequency shown in Figure 10 (e) descends thus.In addition, t3 when the beginning of operating stably t3～t4, compare with the contribution of the rising of the duty ratio of the output of sequential control portion 41, the contribution of the minimizing of the duty ratio of adjusting control part 44 is bigger, the both end voltage of controlling electricity consumption container C 103 thus descends, but in the example of Figure 10, the contribution of the decline of current detection voltage is bigger than the low contribution of the both end voltage of control electricity consumption container C 103, operating frequency descends thus, and the variation of operating frequency as a whole becomes with the example of the Fig. 1 shown in the execution mode 1 same.

Action as t3～t4 in the operating stably, particularly for example bright more by the 63 detected lightnesses of lightness transducer, then reduce more to regulate control part 44 output duty ratio and operating frequency is uprised, reduce from the output power of resonant structure 22 to discharge lamp La.By above-mentioned action, can when keeping the lightness that comprises from the light (so-called exterior light) of the light source beyond the discharge lamp La, suppress power consumption.

In addition, if the light of discharge lamp La is incided in the lightness transducer 63, then also can carry out with outer light irrelevant and the light of discharge lamp La exported be maintained certain control.

In addition, circuit structure is not limited to the structure of Fig. 9, for example on control electricity consumption container C 103, do not connect and regulate control part 44, and be connected the control of oscillating portion 33 with on the operational amplifier OP2 via voltage follower OP1 equally with the example of the Fig. 5 shown in the execution mode 1, on the other hand, about regulating control part 44, as shown in figure 11, also can the adjusting electricity consumption container C 31 that both end voltage is changed according to the output of regulating control part 44 additionally be set with control electricity consumption container C 103.Control electricity consumption container C 103 in the example of adjusting electricity consumption container C 31 and Fig. 9 is same, one end is connected input and regulates on the control part 44 with being connected on the non-counter-rotating input terminal of operational amplifier OP3 and via resistance R 107, other end ground connection, resistance R 108 also is being connected in parallel.In addition, in Figure 11, omitted the diagram of resistance R 103, R104 and the voltage follower OP1 of control electricity consumption container C 103 and periphery thereof.Example about the part beyond above-mentioned and Fig. 9 is common, omits about the diagram and the explanation of common part.In the case, when design, need consider to make adjusting electricity consumption container C 31 also in dwell time T1, fully to discharge equally with control electricity consumption container C 103.But the example of Fig. 9 is compared with the example of Figure 11 has the advantage that can reduce the parts number of packages.

Here, in the circuit of the circuit of Fig. 9 and Figure 11, shown in Figure 12 (a), Figure 12 (b), to the input voltage Vop-cyclical movement of input with the counter-rotating input terminal of operational amplifier OP3.Shown in Figure 12 (a), as long as it is enough high with the higher limit of the input voltage Vop-of the counter-rotating input terminal of operational amplifier OP3 with respect to the input voltage Vop+ of non-counter-rotating input terminal from operational amplifier OP3 to input that use to input, just as shown in figure 13, from resonant structure 22 to the output power of discharge lamp La (below be called " lamp electric power ") with respect to input voltage Vop+ dull increase of input with the non-counter-rotating input terminal of operational amplifier OP3.But, during temperature is very high around high temperature or during the low-down low temperature of environment temperature, because the variation of the characteristic of discharge lamp La, the output power deficiency of driving power portion 5, the control that lamp electric power is increased according to current detection voltage becomes and does not catch up with.For example, shown in Figure 12 (b), becoming to input with the higher limit of the input voltage Vop-of the counter-rotating input terminal of operational amplifier OP3 always than to input during with the low temperature of the low state of the input voltage Vop+ of the non-counter-rotating input terminal of operational amplifier OP3 etc., become than under controlling with the high situation of the output voltage of operational amplifier OP2 at the output voltage of input with operational amplifier OP3, input no longer reflects operating frequency with the output of operational amplifier OP3, with operating frequency is fixed on the lower frequency limit of regulation with the change (being the change of current detection voltage) of the input voltage Vop-of the counter-rotating input terminal of operational amplifier OP3 is irrelevant to input.Thus, in the present embodiment, lamp electric power is as using among Figure 14 shown in the curve PLa, as long as environment temperature be in the prescribed limit just the change by operating frequency be maintained necessarily, when low temperature or during high temperature, by operating frequency being fixed as above-mentioned lower frequency limit, along with environment temperature is left and reduced from the afore mentioned rules scope.Thereby, from resonant structure 22 to the output current of discharge lamp La (below be called " lamp current ") as Figure 14 with shown in the curve ILa, environment temperature is left increase from the central authorities of afore mentioned rules scope as a whole, but when low temperature or during high temperature by as described above operating frequency being fixed, compare with time in environment temperature is the afore mentioned rules scope thus, the recruitment that the variation of environment temperature brings tails off.That is, in the present embodiment, in the time of can preventing low temperature or the lost of life of the discharge lamp La that causes of the excessive increase of the lamp current during high temperature.

(execution mode 4)

The basic structure of present embodiment and execution mode 3 are common, so give identical label and omit explanation for common part.

Present embodiment replaces the lightness transducer 63 of execution mode 3 and possesses the dim signal input part 64 that is transfused to the dim signal that the light output of discharge lamp La is indicated as shown in Figure 15, regulate control part 44 and in operating stably, move, so that the light output of discharge lamp La is changed according to the dim signal that is input in the dim signal input part 64.Dim signal input part 64 is same with the transducer 62 of execution mode 2, will control the control voltage vcc 1 of power supply unit 33 outputs as power supply.In addition, use in the integrated circuit 4 in control, be provided with dim signal judging part 43f, this dim signal judging part 43f judges the kind that is input to the dim signal in the dim signal input part 64, if and be input to signal that dim signal in the dim signal input part 64 is pilot light output then will be input to corresponding to the signal of telecommunication of the content of dim signal and regulate in the control part 44, be that the indication signal of lighting a lamp or turning off the light then will be input to corresponding to the signal of telecommunication of the content of dim signal stops in the control part 42 if be input to dim signal in the dim signal input part 64.

General dim signal is the pwm signal that transmits via the holding wire that is connected on the dim signal input part 64, frequency is 100Hz～1kHz, is the signal of turning off the light that the high more light of the high more then indication of duty ratio is exported, indicated discharge lamp La by the duty ratio below the lower limit of regulation.In addition, dim signal is not limited to the above, also can be to export the analog signal of corresponding voltage value or the digital signal of exporting by the numerical data pilot light with the light of indication.In either case dim signal input part 64 and dim signal judging part 43f can both realize by known technology, so detailed explanation and diagram are omitted.By said structure, can carry out lighting a lamp/turning off the light and the controls such as change of light output according to the discharge lamp La that carries out from the dim signal of outside.In addition, from the accepting of the input of dim signal input part 64 time, for example consume under the situation of electric power by A/D conversion etc. at dim signal judging part 43f, the conducting control of discharge lamp La by the situation of carrying out beyond the dim signal under, if dim signal judging part 43f does not does not accept the input from dim signal input part 64 when starting during to the beginning of operating stably, then always accept to compare with integrated circuit 4 and can reduce consumption electric power from the situation of the input of dim signal input part 64 with control.

Here, control has the clock portion 45 that generates clock signal with integrated circuit 4, the frequency of the clock signal that clock portion 45 generates (below be called " clock frequency ") is high more, fast more in control with the action of each one beyond the clock portion in the integrated circuit 4 45, for fast more with the response of the input of unusual judging part 61 grades of integrated circuit 4 outsides from control, control increases more with the consumption electric power of integrated circuit 4 on the other hand.

And, in the present embodiment,, adopted in the stopping of drive division 31 at least than the structure that in the lighting a lamp of discharge lamp La clock frequency is reduced in view of the speed that in the stopping of drive division 31, does not need response as described above especially.

If explain, then in driving, be provided with report power supply unit 30 with integrated circuit 3, report power supply unit 30 stop execution portion 34 make drive division 31 action during, promptly after the output of the control voltage vcc 1 shown in Figure 16 (a) begins to pass through dwell time T1 and from stop execution portion 34 to be output as the H level shown in Figure 16 of drive division 31 or startup portion 32 (b), shown in Figure 13 (d), produced like that drive division 31 output during, shown in Figure 16 (c), export the report voltage vcc 3 of regulation like that.In the present embodiment, oscillating portion 35 will be reported voltage vcc 3 as power supply, promptly stop execution portion 34 and stop by the input that will reporting voltage vcc 3 when above-mentioned output is made as the L level, and oscillating portion 35 and drive division 31 stop respectively thus.

And then above-mentioned report voltage vcc 3 also is imported into control with in the clock portion 45 of integrated circuit 4.Clock portion 45 shown in Figure 16 (e), make not input report voltage vcc 3 during clock frequency TA than imported report voltage vcc 3 during clock frequency TB low.Thus, realized in the stopping of drive division 31, making action low in the action of clock frequency ratio drive division 31.

According to said structure, thereby make the clock frequency step-down can reduce consumption electric power before beginning by action, thereby and by in the lighting a lamp of discharge lamp La, clock frequency being uprised at least can to accelerate for from the response of control with the input of the outside of integrated circuit 4 at drive division 31.

In addition, clock frequency is as long as raising is just passable in the lighting a lamp of discharge lamp La, be not limited to the timing (when being the beginning of preheating action) that the input of report voltage vcc 3 as described above begins so clock portion 45 improves the timing of clock frequencies, just can before the beginning of the operating stably (time) so long as when starting the end of action.

In addition, use in the integrated circuit 4 in the control of present embodiment, can be by during 31 actions of report voltage vcc 3 identification drive divisions, so also can be during input report voltage vcc 3 not make sequential control portion 41 in (be drive division 31 stop during), regulate control part 44 and do not generate output to oscillating portion 35.If adopt this structure, then with sequential control portion 41 and regulate control part 44 and in the stopping of drive division 31, also generate to the situation of the output of oscillating portion 35 and compare, can realize the minimizing of the consumption electric power in the stopping of drive division 31, relax requirement thereupon, can realize driving miniaturization thus with integrated circuit 3 for the durability of the circuit element of startup portion 32 etc.

(execution mode 5)

The basic structure of present embodiment and execution mode 4 are common, so give identical label and omit explanation for common part.

Present embodiment is compared with execution mode 4, dim signal input part 64 is not set, replace, as shown in figure 17, possess the light a lamp timing portion 46 of time timing of the accumulative total of discharge lamp La, regulate control part 44 according to lighting a lamp the time by the accumulative total of timing portion 46 timing, duty ratio in the operating stably is increased gradually, with remedy with accumulative total light a lamp the discharge lamp La that the process of time accompanies light beam low and to make to the output power of discharge lamp La be that the upper limit rises gradually with respect to the ratio of the rated electrical of discharge lamp La (below be called " light modulation than ") with 100%.Thus, play light modulation from the use of beginning discharge lamp La than reach 100% during, the light beam of discharge lamp La can be remained roughly certain.More particularly, for example as shown in figure 18, when the accumulative total time of lighting a lamp is 0, the light modulation ratio is made as 70%, before the light modulation ratio reaches 100%, makes light modulation, after the light modulation ratio reaches 100%, the light modulation ratio is maintained 100% than rising with linearity with respect to the accumulative total time of lighting a lamp.In the example of Figure 18, make light modulation longer than light a lamp time rated life time of time ratio discharge lamp La of the accumulative total that reaches 100%.As the action of time decision light modulation of lighting a lamp according to accumulative total than (strictly saying it is the duty ratio of regulating the output of control part 44), both can in the such memory of the storage part for example described later that has with integrated circuit 4 of control 47, keep in advance representing totally to light a lamp the time, also can realize by computing with the tables of data of the relation of light modulation ratio and by using this tables of data to realize.

And then, timing portion 46 is also to accumulative total timing service time as service time of discharge lamp ignition device self, if reach time device lifetime (for example 10 years) service time as the regulation in life-span of discharge lamp ignition device by the accumulative total of timing portion 46 timing, then stopping control part 42 will be made as the H level to the output that stops execution portion 34 that drives with integrated circuit 3, and the action of drive division 31 is stopped.Thus, can prevent abnormal heating that the life-span because of circuit element brings etc.

Be described more specifically the structure that accumulative total is lit a lamp the time and added up timing service time.Control has the storage part 47 that is made of nonvolatile memory with integrated circuit 4, discharge lamp La turn off the light during in accumulative total lit a lamp time and totally leaving in the storage part 47 service time.Timing portion 46 reads in the accumulative total that leaves in the storage part 47 and lights a lamp time and accumulative total service time when starting, for example begin before the preheating action, begins the timing that accumulative total is lit a lamp time and accumulative total service time.Light a lamp the time as accumulative total, in the time of both can be, in the time of also can be to the length gauge of time of carrying out operating stably to the length gauge of time of input report voltage vcc 3.As accumulative total service time, during to the length gauge of for example time of input report voltage vcc 3.Under which kind of situation, all timing portion 46 is written to light a lamp time and accumulative total of the accumulative total in the timing respectively in the storage part 47 service time when power supply is disconnected.In addition, accumulative total service time is because the service time of expression discharge lamp ignition device self, thus be not reset, and the accumulative total time of lighting a lamp when having changed discharge lamp La, need reset (returning to 0).As the timing that the accumulative total time of lighting a lamp is resetted, for example both can when detecting no-load condition, the accumulative total time of lighting a lamp be resetted, the switch of operating in the time of also can being arranged on the replacing of discharge lamp La (not shown) resets the accumulative total time of lighting a lamp when having operated this switch.

Here, before accumulative total is lit a lamp time or accumulative total are written in the storage part 47 service time, need to remain on accumulative total in the storage part 47 light a lamp time or accumulative total deletion service time.And, general consume electric power respectively during fashionable and deletion writing of memory, so make deletion and writing under the continuous mutually situation, it is elongated to consume the big time of the temporary change of electric power.So, will stop control part 42 and regulate the data that use in the action of control part 44 promptly power supply be disconnected during in should remain on the light a lamp timing of data such as time and accumulative total service time (below be called " ephemeral data ") deletion of accumulative total in the storage part 47 and separate with the timing that writes ephemeral data, this can shorten in order to carry out the deletion of storage part 47 and to write and during consuming big each of the temporary change of electric power, so be preferred.As ephemeral data as described above, light a lamp time and accumulative total service time except accumulative total, it will also be appreciated that power supply is switched on the number of times of disconnection and turn off the light light modulation before tight of discharge lamp La is compared etc.

And then, for the deletion of storage part 47 and the processing that writes etc. from shortening viewpoint to the time that above-mentioned processing spent of storage part 47, preferably not make clock frequency lower during in carry out and make clock frequency higher during in carry out.

More than comprehensive, in the present embodiment, when the timing that deletion is added up the time of lighting a lamp and adds up service time is made as the beginning of operating stably.In addition, even clock portion 45 had been stopped the supply of report voltage vcc 3 before finishing to writing of storage part 47, before finishing, do not make the clock frequency step-down to writing of storage part 47 yet.The above-mentioned action of clock portion 45 both can realize by the control of timing portion 46, also can will higher clock frequency keep the structure of enough stipulated times that writes to storage part 47 and realized by making in the back clock portion that stops of report voltage vcc 3.Present embodiment is passed through said structure, with to the deletion of storage part 47 with write the situation of carrying out continuously mutually, and make clock frequency lower during in carry out the deletion of storage part 47 and situation about writing are compared, the consumption electric power big time of temporary change is shortened, reduced the electric stress that acts on driving power portion 5 grades.

(execution mode 6)

The basic structure of present embodiment and execution mode 5 are common, so give identical label for common part, omit diagram and explanation.

Present embodiment possesses the power supply test section 165 of output and direct voltage that the voltage of the output voltage smoothing of rectification part DB is corresponding as shown in figure 19.In addition, the low of voltage from AC power AC input (below be called " input supply voltage ") judged based on the output of power supply test section 165 by the execution portion 34 that stops of present embodiment, when being judged as input supply voltage when low, equally output is made as the L level when becoming the H level, drive division 31 and report power supply unit 30 are stopped with the output that stops control part 42.

If specifically describe, then power supply test section 165 as shown in figure 20, output with the output voltage of rectifier DB with the divider resistance dividing potential drop and with capacitor level and smooth direct voltage.In addition, stop that execution portion 34 possesses the 5th reference voltage Vr5 that is transfused to regulation in non-counter-rotating input terminal and the input comparator CP4 that in the counter-rotating input terminal, is transfused to the output voltage of power supply test section 165, non-counter-rotating input terminal is connected and stops on the control part 42 and be transfused to the input comparator CP5 of the 5th reference voltage Vr5 in the counter-rotating input terminal, export above-mentioned two input comparator CP4, the logic of the output of CP5 and logic and circuit OR2, the constant current source Ir2 of delay electricity consumption container C 105 chargings that drive the outside of using integrated circuit 3 will be located at, constitute and be connected the switch element Q106 that postpones on the electricity consumption container C 105 and in grid, be transfused to the output of logic and circuit OR2 side by side by the FET of n channel-type, and the output comparator CP6 that in the counter-rotating input terminal, is transfused to the 6th reference voltage Vr6 of regulation in connection delay electricity consumption container C 105 on the non-counter-rotating input terminal.This output comparator CP6 be output as the H level during during drive division 31 and the action of report power supply unit 30, be output report voltage vcc 3 during.

The above-mentioned action that stops execution portion 34 is described.Stop execution portion 34 by will be from the control voltage vcc 1 of control power supply unit 33 output as power supply, the charging that postpones electricity consumption container C 105 is begun with the output from the control voltage vcc 1 of controlling power supply unit 33, when the both end voltage that postpones electricity consumption container C 105 has reached the 6th reference voltage Vr6, output by output comparator CP6 becomes the H level, begin the action of drive division 31 and the output of report voltage vcc 3, at this moment, in startup portion 32, switch element Q101 is fixed to off-state.That is, will postpone the capability value and the product of the 6th reference voltage Vr6 of electricity consumption container C 105, with the output current of the constant current source Ir2 that stops execution portion 34 except that and the charging interval T2 (with reference to Figure 21) that obtains is consistent with dwell time T1.

In addition, be lower than under the situation of the 5th reference voltage Vr5 at the output voltage of power supply test section 165 or stopping under the situation that control part 42 is output as the H level, output by any input comparator CP4, CP5 becomes the H level and with switch element Q106 conducting, to postpone electricity consumption container C 105 via switch element Q106 thus discharges sharp, the both end voltage that postpones electricity consumption container C 105 is lower than the 6th reference voltage Vr6 and the output of output comparator CP6 becomes the L level, carries out stopping of drive division 31 and report voltage vcc 3 thus.Here, time (below be called " the retention time ") T3 (with reference to Figure 21) that becomes the L level from the output that switch element Q106 is disconnected to output comparator CP6 becomes enough short.

An example of the action of expression present embodiment in Figure 21.In the example of Figure 21, become the moment of L level in the output that stops control part 42 shown in Figure 21 (a), the output voltage of the power supply test section 165 shown in Figure 21 (b) is lower than the 5th reference voltage Vr5, the output of an input comparator CP4 shown in Figure 21 (c) is the H level thus, thereby the output of logic shown in Figure 21 (d) and circuit 2 also becomes the H level.If the output voltage of final power supply test section 165 surpasses the 5th reference voltage Vr5, then the output of logic and circuit OR2 becomes the L level and switch element Q106 is disconnected, and begins to postpone the charging of electricity consumption container C 105 thus.And then if through charging interval T2, the both end voltage that postpones electricity consumption container C 105 reaches the 6th reference voltage Vr6, and then the output of output comparator CP6 becomes the H level, the action of beginning drive division 31 and the output of the report voltage vcc 3 shown in Figure 21 (f).Then, if the output voltage of power supply test section 165 descends and is lower than the 5th reference voltage Vr5, then the output of output comparator CP6 becomes the L level in very short retention time T3, here, the action of drive division 31 and the output of report voltage vcc 3 is stopped respectively.

In addition,,, when beginning to report the input of voltage vcc 3, begin to move a series of action of operating stably with in the integrated circuit 4 in the control of present embodiment from preheating.

In addition, power supply test section 165 and the structure that stops execution portion 34 are not limited to the above, for example as shown in figure 22, also can adopt following structure: in power supply test section 165, append the switch element that the transistor by the npn type of the charging voltage that is transfused to capacitor in base stage, grounded emitter constitutes, and the collector electrode of this switch element is connected on the non-counter-rotating input terminal of the input comparator CP5 common with stopping control part 42.That is, power supply test section 165 according to the output voltage of rectification part DB by electric resistance partial pressure and by capacitor level and smooth voltage with respect to the conducting voltage of switch element is high or low output is changed.Select to constitute each element of power supply test section 165 so that when the output voltage of rectification part DB is enough high with the switch element conducting of power supply test section 165 if the low state of input voltage of the output voltage deficiency of rectification part DB then with the switch element disconnection of power supply test section 165.In the example of Figure 22, power supply test section 165 is connected via resistance R 51 on the output (control voltage vcc 1) of control power supply unit 33 with the tie point that stops execution portion 34, in resistance R 51 and stop to have appended between the control part 42 resistance R 52.Make by these resistance R 51, R52 and will control voltage vcc 1 voltage after partial than the 5th reference voltage Vr5 height, even stop the output of control part 42 are L level, if the switch element of power supply test section 165 is disconnected, then make the output that stops execution portion 34 become the L level and carry out stopping of drive division 31 grades by the low state of input voltage.Perhaps, also can be made as following action: will to control voltage vcc 1 voltage after partial by resistance R 51, R52 lower than the 5th reference voltage Vr5 if make, and is that H level and the output that stops the input comparator CP5 of execution portion 34 when being the low state of input voltage become the H level and makes the output that stops execution portion 34 become the L level in the output that stops control part 42 only then.In the structure of Figure 22, circuit structure is oversimplified by the input comparator CP4 of power supply test section 165 sides among Figure 20 and logic and circuit OR2 being omitted respectively, being compared with the example of Figure 20 on the whole.Here, in the structure of Figure 22, to stop the output of control part 42 irrelevant and will be fixed as the L level to the input of the non-counter-rotating input terminal of input comparator CP5 as the enough Gao Shiyu of the output voltage of rectification part DB, so do not carry out by stopping that the output that stops control part 42 is implemented, if but between power supply test section 165 and input comparator CP5, appended resistance (not shown), then when the output voltage of rectification part DB is enough high, also could implement to stop by the output that stops control part 42.

(execution mode 7)

The basic structure of present embodiment and execution mode 6 are common, so give identical label for common part, omit diagram and explanation.

As shown in figure 23, in the preheating part 23 of present embodiment, between the once coiling of transformer Tr1 and earthing potential, appended switch element Q3.This switch element Q3 carries out conducting by sequential control portion 41 and disconnects control, is switched in the preheating action at least, is disconnected in operating stably at least on the other hand.Thus, comparing with the situation that switch element Q3 is not set can lowly meaningless power consumption.

In addition, in the present embodiment, be divided into and generate according to whether being the non-loaded test section 61a of the output that changes of no-load condition and judging whether to be no-load condition and will to be input to the non-loaded judging part 43b that stops in the control part 42 detecting unusual judging part 61 as the no-load condition of abnormality corresponding to the output of judged result based on the output of non-loaded test section 61a, with non-loaded judging part 43b integrated in control with in the integrated circuit 4.As non-loaded test section 61a, for example can use detection will be connected the circuit of the impedance between terminal on each end of filament of discharge lamp La, non-loaded test section 61a and non-loaded judging part 43b can realize by known technology, so omit detailed diagram and explanation.

And then, the output of power supply test section 165 is not to stopping execution portion 34 but imports with integrated circuit 4 to control,, be provided with output based on power supply test section 165 and judge whether to be the abnormality (below be called " the low state of input voltage ") of input supply voltage deficiency and will to be input to the low judging part 43c of the input voltage that stops in the control part 42 with in the integrated circuit 4 in control corresponding to the output of judged result.To supply with the situation (being the situation that power supply is disconnected) that is stopped to the electric power of rectification part DB from AC power AC and also be judged as the low state of input electric power.

And, stop control part 42 termly with reference to the output of non-loaded judging part 43b and the output of the low judging part 43c of input electric power, if in any of non-loaded judging part 43b and input electric power low judging part 43c, be judged as abnormality, then will be made as the H level, and sequential control portion 41, adjusting control part 44 and timing portion 46 are stopped respectively to the output that drives with integrated circuit 3.Before the beginning of preheating action, be judged as under the situation of abnormality, be maintained the H level, do not begin the action of drive division 31 by the output that will stop control part 42.In addition, when stopping because of the judgement of no-load condition, timing portion 46 resets the accumulative total time of lighting a lamp, and will not have the accumulative total time of lighting a lamp of timing to abandon.

(execution mode 8)

The basic structure of present embodiment and execution mode 5 are common, so give identical label for common part, omit diagram and explanation.

In the present embodiment, replace unusual judging part 61, as shown in figure 24, be provided with parameter that detection changes and output life tests portion 66 when the end of lifetime of discharge lamp La corresponding to the voltage of detected parameter.Particularly, the asymmetrical current that produces detects as above-mentioned parameter in the life tests portion 66 of present embodiment in discharge lamp La, export the voltage corresponding with it.

In addition, use in the integrated circuit 4 in control, the output that is provided with based on life tests portion 66 judges whether that being is the end of lifetime state of the abnormality of end of lifetime as discharge lamp La, and will be input to the discharge lamp judging part 43d that stops in the control part 42 corresponding to the output of judged result.

If explain, then as shown in figure 25, life tests portion 66 possess an end via the inductor L1 that the filament of resistance R 111 and discharge lamp La is connected resonant structure 22 go up, the capacitor C106 of other end ground connection and the parallel circuits of resistance R 113.In addition, capacitor C106 is connected on the discharge lamp judging part 43d via the diode D103 that makes negative electrode towards capacitor C106, and the tie point of this diode D103 and discharge lamp judging part 43d is connected on the output (control voltage vcc 1) of control power supply unit 33 via resistance R 112.

Here, at discharge lamp La is not under the situation of end of lifetime, in the lighting a lamp of discharge lamp La, Idc-mutually about equally to the electric current of resonant structure 22 (below be called " outflow electric current ") to the electric current of life tests portion 66 (below be called " inflow current ") Idc+ and from life tests portion 66 from resonant structure 22.Thus, the both end voltage of the capacitor C106 of life tests portion 66, be that the output voltage of life tests portion 66 is maintained roughly certain voltage (below be called " normal voltage "), this normal voltage is about control voltage vcc 1 usefulness resistance R112, R113 voltage after partial.In addition, the tie point of the inductor L1 of resonant structure 22 and discharge lamp La is connected via resistance R 114 on the output of high-voltage side of DC power supply portion 1.

On the other hand, if discharge lamp La becomes end of lifetime, the consumption that then is coated in the radiation body on the filament in discharge lamp La produces difference in each filament, one of above-mentioned electric current I dc+, Idc-becomes than another big (promptly producing asymmetrical current), between the output voltage and above-mentioned normal voltage of life tests portion 66, poor corresponding to above-mentioned electric current I dc+, Idc-poor (size of asymmetrical current) taken place.For example, under the situation that outflow electric current I dc+ is Duoed than inflow current Idc-, the output voltage of life tests portion 66 becomes than above-mentioned normal voltage height, otherwise under the situation that outflow electric current I dc+ lacks than inflow current Idc-, the output voltage of life tests portion 66 becomes and forces down than above-mentioned normal electrical.

Discharge lamp judging part 43d compares the output voltage of life tests portion 66 lower voltage limit with the regulation of forcing down than the high set upper limit voltage of normal voltage and than normal electrical respectively, if to be upper voltage limits following and more than the lower voltage limit then be judged as and be not the end of lifetime state for the output voltage of life tests portion 66, if the output voltage of life tests portion 66 surpasses upper voltage limit or is lower than lower voltage limit then is judged as the end of lifetime state.For example, be that 5V, normal voltage are under the situation of 2.5V at control voltage vcc 1, upper voltage limit is made as 4V and lower voltage limit is made as 1V.

Be judged as the end of lifetime state if stop control part 42 by discharge lamp judging part 43d, then will be made as the H level to the output that drives with integrated circuit 3, drive division 31 grades that drive with integrated circuit 3 are stopped, and sequential control portion 41 and adjusting control part 44 are stopped respectively.

And then, according on the resistance R 111 of life tests portion 66, whether connecting the filament of discharge lamp La, promptly whether be no-load condition, the both end voltage difference of the capacitor C106 of life tests portion 66.Thereby, also the output of life tests portion 66 can be used for the detection (judgement) of no-load condition.But, owing to also considered before the action of drive division 31 begins, also flow among the capacitor C106 of life tests portion 66 via resistance R 114 and preheat circuit 23 from the electric current of DC power supply portion 1, so be used in output under the situation of detection of no-load condition with life tests portion 66, need make the time constant of life tests portion 66 shorter, so that the omission that the charging of the capacitor C106 under the electric current as described above causes survey does not take place after can not beginning in the action of drive division 31 at least than dwell time T1.

(execution mode 9)

The basic structure of present embodiment and execution mode 6 are common, so give identical label for common part, omit diagram and explanation.

The DC power supply portion 1 of present embodiment is a known so-called boost chopper (booster converter) as shown in figure 26.Particularly, possess between the dc output end that is connected rectification part DB on the series circuit of the inductor L2 of (being between the dc output end and earthing potential of high-voltage side of rectification part DB) and diode D1 and output capacitor C6 and the tie point that an end is connected inductor L2 and diode D1 and the switch element Q4 of other end ground connection and the series circuit of resistance R 5, with the both end voltage of output capacitor C6 as output voltage, the duty ratio control output voltage of the switch element Q4 that disconnects by the periodicity conducting.Generally, if use the such Switching Power Supply of booster converter, then the improvement owing to power factor consumes the electric power minimizing.

And then present embodiment for example possesses the DC power supply test section 167 by the voltage that the divider resistance with the output voltage dividing potential drop of DC power supply portion 1 constitutes, the high more then output of output voltage of DC power supply portion 1 is high more.In addition, as the example of Figure 20, use the high more unit of then exporting high more voltage of effective value of the output voltage of rectification part DB as power supply test section 165.

In addition, with in the integrated circuit 3, be provided with the circuit of the switch element Q4 that is used for driving DC power supply portion 1 in the driving of present embodiment.If explain, then driving, be provided with the voltage mistake amplifier OP4 of output corresponding to the difference of the output voltage of the 7th reference voltage Vr7 that stipulates and DC power supply test section 167 with in the integrated circuit 3, multiplier 36a with the output multiplication of the output of power supply test section 165 and wrong amplifier OP4, be transfused to the output of multiplier 36a in the input terminal but not the counter-rotating input terminal is connected the comparator C P7 on the tie point of the switch element Q4 of DC power supply portion 1 and resistance R 5 in counter-rotating, in reseting terminal, be transfused to the flip-flop circuit 36b of the output of comparator C P7, and go up and the switch element Q4 conducting of DC power supply portion 1 is disconnected the 36c of power drives portion that drives according to the output of flip-flop circuit 36b via the switch element Q4 that resistance R 4 is connected DC power supply portion 1.

And then, on the inductor L2 of DC power supply portion 1, being provided with 2 coilings of an end ground connection, the other end of these 2 times coilings is connected to be located at and drives with on the 36d of zero current detection portion in the integrated circuit 3.The 36d of zero current detection portion is connected being provided with on the terminal of flip-flop circuit 36c, voltage based on induction in above-mentioned 2 coilings detects the exergonic of inductor L2 and finishes, and to flip-flop circuit 36b when detecting exergonic the finishing of inductor L2 the terminal input pulse is set.

Thus, the switch element Q4 of DC power supply portion 1 is periodically carried out conducting disconnect and driving, its duty ratio of FEEDBACK CONTROL is so that the output voltage of DC power supply portion 1 becomes the target voltage of regulation.This target voltage is to make the output voltage of DC power supply test section 167 become the voltage of the 7th reference voltage Vr7.

And then, driving with in the integrated circuit 3, be provided with output based on DC power supply test section 167 and judge whether it is the abnormality (below be called " the low state of direct voltage ") of output voltage deficiency of DC power supply portion 1 and output the low judging part 37 of direct voltage corresponding to the voltage of judged result.If specifically describe, then the low judging part 37 of direct voltage possesses the output voltage that is transfused to DC power supply test section 167 in non-counter-rotating input terminal and be transfused to the comparator C P8 of the 8th reference voltage Vr8 of the regulation lower than the 7th reference voltage Vr7 and the switch element Q107 that the FET by the n channel-type on the lead-out terminal that grid is connected this comparator C P8 constitutes in the counter-rotating input terminal as shown in figure 27.The end ground connection of this switch element Q107 and be transfused to report voltage vcc 3 via resistance R 32 in the other end, the tie point of this switch element Q107 and resistance R 32 is connected on the control usefulness integrated circuit 4 as the output of the low judging part 37 of direct voltage.Above-mentioned the 8th reference voltage Vr8 is made as 50%～80% of the 7th reference voltage Vr7 corresponding with target voltage.Promptly, the low judging part 37 of direct voltage when the output voltage of DC power supply test section 167 be that the 8th reference voltage Vr8 is not judged as the low state of direct voltage when above and output is made as the L level, when the output voltage of DC power supply test section 167 is lower than the 8th reference voltage Vr8, be judged as the low state of direct voltage, output is made as the H level.For example, be under 80% the situation of the 7th reference voltage Vr7 making the 8th reference voltage Vr8, when about low state of direct voltage that is judged as 80% time of the output voltage fall short voltage of DC power supply portion 1.

In addition,, be provided with the output proper transformation of the low judging part 37 of direct voltage is input to the judgement input part 144 that stops in the control part 42 with in the integrated circuit 4 in control.

And then present embodiment and execution mode 8 are same, possess life tests portion 66 and discharge lamp judging part 43d.

Present embodiment stop control part 42 at any time with reference to the output of discharge lamp judging part 43d with judge the output of input part 144, if 43d is judged as the end of lifetime state by the discharge lamp judging part, then will be made as the H level to the output that drives with integrated circuit 3 equally with execution mode 8, drive division 31 grades that drive with integrated circuit 3 are stopped, and sequential control portion 41 and adjusting control part 44 are stopped respectively.

In addition, stop control part 42 in that low judging part 37 is judged as under the situation of the low state of direct voltage by direct voltage, not that drive division 31 and sequential control portion 41 are stopped immediately, but control sequence control part 41 is restarted time T 5 (with reference to Figure 29) with what will start that action stipulates, if still be judged as the low state of direct voltage through after restarting time T 5, then constantly at this, same when being judged as the end of lifetime state, to be made as the H level to the output that drives with integrated circuit 3, drive division 31 grades that drive with integrated circuit 3 are stopped, and sequential control portion 41 and adjusting control part 44 are stopped respectively.

The action of expression present embodiment in Figure 28 and Figure 29.In Figure 28 and Figure 29, be that the time of the output voltage of (a) expression DC power supply test section 167 changes, the time of the output of the comparator C P8 of the low judging part 37 of (b) expression direct voltage changes, the time of the output of the low judging part 37 of (c) expression direct voltage changes, the time of the output of (d) order of representation control part 41 changes, the time of (e) expression operating frequency changes respectively, (f) expression stops control part 42 and change for the time that drives with the output of integrated circuit 3.Figure 28 represents that the low state of direct voltage (being that the low judging part of direct voltage is the state of H level) is than the action of restarting under the situation about stopping that finishing, do not stop thus control part 42 enforcements in the short time T 4 of time T 5.In addition, Figure 29 represents that the duration of the low state of direct voltage has reached and restarts time T 5, carried out stopping action under the situation about stopping that control part 42 implements thus.In the present embodiment, the execution portion 34 that stops with integrated circuit 3 of driving is when stopping that the 36c of power drives portion is also stopped, in Figure 29, after the end of the startup action that has continued to restart time T 5, by stopping of the 36c of power drives portion, the output voltage of the output voltage of DC power supply portion 1 and DC power supply test section 167 descends.

In addition, when being judged as the low state of direct voltage, make immediately under the situation that drive division 31 and the 36c of power drives portion stop, the low state of direct voltage for example because instantaneous power failure etc. cause, can not make discharge lamp La light a lamp even then eliminated at short notice.To this, in the present embodiment, restart time T 5 by when being judged as the low state of direct voltage, starting action as described above, under the situation that the low state discharge lamp of the direct voltage of short time as described above La sudden strain of a muscle is gone out, discharge lamp La is lit a lamp once more.In addition, under the situation that is judged as the low state of direct voltage after the end that above-mentioned startup of restarting time T 5 is moved, drive division 31 and the 36c of power drives portion are stopped, even, also can avoid by the FEEDBACK CONTROL of mistake the electric stress of overaction on circuit element and discharge lamp La so the output of DC power supply test section 167 does not reflect the output voltage of DC power supply portion 1 and is always under the such situation of 0V for example hindering for some reason.

In addition, the control part 42 that stops of present embodiment is judging under both situation of end of lifetime state and the low state of direct voltage that the action with based on the judgement of the low state of direct voltage serve as preferentially, be judged as the low state of direct voltage during in do not carry out action corresponding to the judgement of end of lifetime state.Its reason be because, if the low state of direct voltage takes place, then consider thus simultaneous for example the sudden strain of a muscle of discharge lamp La go out and lamp current is temporary becomes asymmetric and mistake is judged as the end of lifetime state, if carry out stopping of drive division 31 and the 36c of power drives portion, then might can not carry out startup action in fact based on the judgement of the low state of direct voltage as described above according to such erroneous judgement is disconnected.In addition, for example, operating frequency guarantees the so-called slow action of side mutually by fully being left with respect to the resonant structure 22 and the resonance frequency of the resonant circuit of discharge lamp La formation, can avoid that as described above to knock out the erroneous judgement that causes disconnected, if but like this, then circuit loss increases because idle current increases, so not preferred.

(execution mode 10)

The basic structure of present embodiment and execution mode 9 are common, so give identical label for common part, omit diagram and explanation.

The 36d of zero current detection portion of present embodiment possesses that secondary coiling that the counter-rotating input terminal is connected the inductor L2 of DC power supply portion 1 is gone up and the input comparator CP9 that is transfused to the 9th reference voltage Vr9 of regulation in non-counter-rotating input terminal as shown in figure 30, the single-shot trigger circuit OS of output that when the L level is reversed to the H level, begins the pulse of regulation amplitude when the output of input comparator CP9, the non-inverter circuit INV of the output of output single-shot trigger circuit OS, the 1st logic integrated circuit AND1 of the logic product of the output of the output NAND circuit INV of output input comparator CP9, by being the reservation electricity consumption container C 107 of the constant current source Ir3 charging of power supply with control voltage vcc 1, constitute and be connected in the switch element Q108 that keeps on the electricity consumption container C 107 and on grid, connecting the lead-out terminal of the 1st logic integrated circuit AND1 in parallel by the FET of n channel-type, in the counter-rotating input terminal, be transfused to the 10th reference voltage Vr10 of regulation and on non-counter-rotating input terminal, connecting the output comparator CP10 that keeps electricity consumption container C 107, and the 2nd logic integrated circuit AND2 that the logic product of the output of the output of output comparator CP10 and single-shot trigger circuit OS is exported as the output of the 36d of zero current detection portion.

Utilize Figure 31 that the action of the 36d of zero current detection portion is described.The situation that consideration changes shown in (b) Figure 31 to the input voltage of the 36d of zero current detection portion like that from 2 coilings of the inductor L2 of DC power supply portion 1.So the output of input comparator CP9 becomes among Figure 31 such shown in (c), the output of single-shot trigger circuit OS becomes among Figure 31 such shown in (e).Keeping electricity consumption container C 107 is discharged sharp via switch element Q108 when the 1st logic integrated circuit AND1 is output as the H level, so during the output L of the 1st logic integrated circuit AND1 level, be input comparator CP9 be output as the L level during and single-shot trigger circuit OS be output as the H level during in be recharged, the output voltage to output comparator CP10 is risen gradually.Here, the 36d of zero current detection portion among Figure 31 shown in (g) be output as the H level during be during the output of single-shot trigger circuit OS is the output H level of H level and output comparator CP10, promptly in Figure 31 the output of the output comparator CP10 shown in (f) be reversed to from the H level output before tight, single-shot trigger circuit OS of L level the pulse duration amount during, thus, the output of the 36c of power drives portion becomes among Figure 31 output such shown in (a).As long as the output of output comparator CP10 is not the H level, then the output of the 36d of zero current detection portion does not just become the H level, so after the input voltage to the 36d of zero current detection portion is lower than the 9th reference voltage Vr9, among the retention time T6 of the regulation before the both end voltage that keeps electricity consumption container C 107 has reached the 10th reference voltage Vr10, the output of the 36d of zero current detection portion does not become the H level.In other words, as long as to the input voltage of the 36d of zero current detection portion be lower than the 9th reference voltage Vr9 during duration do not reach above-mentioned retention time T6, the output of flip-flop circuit 36b does not just become the H level, thereby the switch element Q4 of DC power supply portion 1 is not switched on.

In addition, in DC power supply portion 1, because the contrary recovery time of spurious impedance and diode D1, after switch element Q4 just has been switched on, flows to detection from the electric current of output capacitor C6 (below be called " adverse current electric current ") and hinder among the R3.In addition, driving, descending if the input voltage input supply voltage of the counter-rotating input terminal of the comparator C P7 on the reseting terminal that is connected flip-flop circuit 36b descends with in the integrated circuit 3.And, become under the situation of H level with respect to above-mentioned countercurrent electric rheology output low, above-mentioned comparator C P7 at input supply voltage, although do not put aside energy fully in inductor L2, switch element Q4 also is disconnected.In the case, though can be disconnected once more with above-mentioned same switch element Q4, can expect repeatedly and switch element Q4 is switched on disconnection with the short cycle by this once more with switch element Q4 conducting in the very short time.If switch element Q4 is switched on disconnection with the short cycle like this, then the electric stress of overaction on switch element Q4.

With respect to this, in the present embodiment, as mentioned above, as long as to the input voltage of the 36d of zero current detection portion be lower than the 9th reference voltage Vr9 during duration do not reach retention time T6, just not with the switch element Q4 conducting of DC power supply portion 1, the off-state that is switch element Q4 continues retention time T6 at least, even so near the situation that the input voltage of the 36d of zero current detection portion fine changes as the right-hand member of Figure 31 also can be avoided the conducting disconnection lost of life such situation of the switch element Q4 of DC power supply portion 1 because of the short cycle.

And then, in the present embodiment, the output of the 36d of zero current detection portion is connected being provided with on the terminal of flip-flop circuit 36b via logic and circuit OR3, driving with in the integrated circuit 3, be provided with the output that monitors flip-flop circuit 36b, when being the L level more than the lasting stipulated time of the output of flip-flop circuit 36b via above-mentioned logic and circuit OR3 the 36e of the portion that begins again that the terminal input pulse is set to flip-flop circuit 36.

Here, in execution mode 5, when totally having reached time device lifetime, drive division 31 grades are stopped service time, with respect to this, in the present embodiment, do not carry out stopping of drive division 31 grades even totally reached the time device lifetime service time yet, when totally having reached time device lifetime, carry out other actions service time.Below explain.

Use in the integrated circuit 4 in the control of present embodiment, shown in figure 32, be provided with report portion 48, according to accumulative total whether be service time time device lifetime with on switch output, so that by accumulative total service time (being the service time of discharge lamp ignition device self) of timing portion 46 timing less than time device lifetime during in make and be output as the L level, be output as the H level by making in during the accumulative total of timing portion 46 timing is more than time device lifetime service time.Time device lifetime for example was made as 30,000 hours.In addition, driving, be provided with the report input part 38 of the output that is transfused to report portion 48 with in the integrated circuit 3.

And, in reporting that input part 38 is during the output H of report portion 48 level, be maintained off-state and the output of output comparator CP10 is fixed as the H level by switch element Q108, with the output of single-shot trigger circuit OS output as the 36d of zero current detection portion with the 36d of zero current detection portion.Thus, no longer carry out the off-state of switch element Q4 is guaranteed the above-mentioned action of retention time T6, so the possibility that is switched on disconnection with the short cycle because of the unusual switch element Q4 of AC power AC uprises the lifetime of switch element Q4 thus.

Here, in can not predicting the source element that constitutes discharge lamp ignition device which reaches under the situation in life-span at first, difficult establishment be used for preventing discharge lamp ignition device to the life-span time the countermeasure of accident.In addition, make service time under the situation that discharge lamp La turns off the light in according to the rules accumulative total as enforcement mode 5, discharge lamp La is turned off the light simultaneously in a plurality of discharge lamp ignition devices of An Zhuaning at the same time, does not wish to take place for the user.With respect to this, in the present embodiment, by above-mentioned action, the fault of the switch element Q4 of DC power supply portion 1 takes place easily, so switch element Q4 uprises than the possibility that other circuit elements reach the life-span more earlier, so establish the countermeasure of known use current fuse (not shown) etc. easily.In addition, the time of fault exists inhomogeneous because switch element Q4 reaches the life-span, even, do not have the situation that discharge lamp La is turned off the light simultaneously when the life-span of these a plurality of discharge lamp ignition devices so begin the situation of the use of a plurality of discharge lamp ignition devices simultaneously yet.

Action when in addition, totally reaching time device lifetime is not limited to the above service time.For example, also can adopt following structure: clock portion 45 according to the output of report portion 48 change be not transfused to report voltage vcc 3 during be clock frequency in the stopping of drive division 31, after totally having reached time device lifetime, it is high before to make above-mentioned clock frequency ratio totally reach the time device lifetime service time service time.More particularly, for example before accumulative total reaches the time device lifetime service time with execution mode 4 make equally be not transfused to report power supply cc3 during clock frequency TA lower than the clock frequency TB in the operating stably, on the other hand, after accumulative total reaches the time device lifetime service time, make be not transfused to report power supply cc3 during clock frequency TA identical with clock frequency TB in the operating stably.In the case, because the electric stress that acts in the stopping of drive division 31 on the 1st switch element Q101 of startup portion 32 becomes big, the 1st switch element Q101 of startup portion 32 reaches the possibility in life-span at first and uprises.If adopt this structure, then the output of report portion 48 is only processed in integrated circuit 4 is used in control, so no longer need report input part 38 be set in driving with integrated circuit 3, can realize driving the miniaturization with integrated circuit 3 thus.

(execution mode 11)

The basic structure of present embodiment and execution mode 10 are common, so give identical label for common part, omit diagram and explanation.

In the present embodiment, as shown in figure 33,, adopt structure as shown in Figure 11 in execution mode 3 as the structure of oscillating portion 35.In addition, in Figure 33, omitted diagram for the circuit of regulating control part 44 and periphery thereof.

In the present embodiment, report input part 38 is connected the 11st reference voltage Vr11 that is transfused to regulation in the report portion 48 and in non-counter-rotating input terminal by the counter-rotating input terminal and lead-out terminal is connected control and constitutes with the comparator C 11 on the counter-rotating input terminal of operational amplifier OP2 via resistance R 33.Make the 11st reference voltage Vr11 lower and than the magnitude of voltage height of the output of the L level of report portion 48, the output of report input part 38 is the output counter-rotating that the output of above-mentioned comparator C 11 makes report portion 48 than the magnitude of voltage of the output of the H level of report portion 48.In addition, by connection as described above, operating frequency shown in Figure 34 (c) report portion 48 shown in (a) in Figure 34 be output as the H level during (be discharge lamp ignition device be judged as end of lifetime during) among T9, the T10, be made as than report portion 48 be output as the L level during (be discharge lamp ignition device be not judged as end of lifetime during) high frequency f 4, the f5 of operating frequency f1, f2 of T7, T8.Thus, shown in Figure 34 (b) from resonant structure 22 to the amplitude of the output voltage of discharge lamp La during the output H of report portion 48 level T9, the T10, for than little amplitude V2, the V4 of amplitude V1, V3 among T7, the T8 during the output L level of report portion 48.And then, the sequential control portion 41 of present embodiment is during the output H of report portion 48 level among T9, the T10, than T7, T8 during the output L level of report portion 48, make duration T 7, the T9 length of preheating action and make the duration T 8, the T10 that start action short.

According to said structure, discharge lamp ignition device be judged as end of lifetime during in, elongated by the duration that makes the preheating action, the life-span of discharge lamp La shortens easily, and by operating frequency is uprised, the startability variation of discharge lamp La is so the user might know the end of lifetime of discharge lamp ignition device.Duration T 9 as the action of the preheating during the output H level of report portion 48, particularly for example be made as 2 times～3 times of duration T 7 of the preheating action during the output L level of report portion 48, the duration that can make the preheating action thus is excessive reliably and make the lifetime of discharge lamp La.And then the duration T 9 of the preheating action during the output H level of report portion 48 is elongated sees the degree of just knowing to the people if make, then the easier end of lifetime of knowing discharge lamp ignition device for the user.

(execution mode 12)

The basic structure of present embodiment and execution mode 11 are common, so give identical label for common part, omit diagram and explanation.

Use in the integrated circuit 3 in the driving of present embodiment; as shown in figure 35, replace the low judging part 37 of direct voltage and be provided with to judge whether it is become unusual high overvoltage condition and when be judged as overvoltage condition, make the overvoltage protection portion 39 of the output voltage decline of DC power supply portion 1 of the output voltage V dc of DC power supply portion 1.In addition, report input part 38 is connected in the overvoltage protection portion 39, and overvoltage protection portion 39 changes action according to the output of report portion 48.

Overvoltage protection portion 39 as shown in figure 36, possess the output that in non-counter-rotating input terminal, is transfused to DC power supply test section 167 and in the counter-rotating input terminal, be transfused to regulation the 12nd reference voltage Vr12 comparator 12 and the logic product of the output of this comparator C P12 and the output of report input part 38 is outputed to logic integrated circuit AND3 in the reseting terminal of flip-flop circuit 36b.Promptly; when totally not reaching the time device lifetime service time; when surpassing the 12nd reference voltage Vr12, the output voltage of DC power supply test section 167 carries out disconnecting the overvoltage protection action that control makes the output voltage V dc decline of DC power supply portion 1 by switch element Q4 to DC power supply portion 1; after totally reaching the time device lifetime service time; because the output of report input part 38 becomes the L level; the output of logic integrated circuit AND3 is fixed to the L level, no longer carries out above-mentioned overvoltage protection action.

According to said structure, after accumulative total had reached the time device lifetime service time, because no longer carry out the overvoltage protection action, the higher electric stress of effect on the switch element Q4 of DC power supply portion 1 easily was so can access the effect same with execution mode 10.Promptly, because switch element Q4 uprises than the possibility that other circuit elements reach the life-span more earlier, so establish the countermeasure of known use current fuse (not shown) etc. easily, in addition, the timing of fault exists inhomogeneous because switch element Q4 reaches the life-span, even, do not have the situation that discharge lamp La is turned off the light simultaneously when the life-span of these a plurality of discharge lamp ignition devices so begin the situation of the use of a plurality of discharge lamp ignition devices simultaneously yet.

In addition; overvoltage protection portion 39 is not limited to the above; also can logic integrated circuit AND3 be set and for example constitute like that as shown in figure 37; the 13rd reference voltage Vr13 of the regulation that the 12nd reference voltage Vr12 and Bi Di 12 reference voltage Vr12 are high is input among the comparator C P12 via the multiplexer TG3 that uses transmission gate circuit to constitute respectively, and the voltage that will be input in during the output H of report portion 48 level in the counter-rotating input terminal of comparator C P12 of overvoltage protection portion 39 is made as the 13rd reference voltage Vr13 higher than the 12nd reference voltage Vr12.If adopt this structure, the voltage that then is input to after accumulative total reaches the time device lifetime service time in the counter-rotating input terminal of comparator C P12 of overvoltage protection portion 39 uprises, and is difficult for carrying out overvoltage protection and moves, and can access same effect thus.

Here, in above-mentioned various discharge lamp ignition devices, rectification part DB, DC power supply portion 1, switch portion 21, resonant structure 22, drive with integrated circuit 3 and control and for example be installed in respectively on as shown in Figure 38 the OBL printed wiring board 70 with integrated circuit 4.In the example of Figure 38, on an end of the length direction of printed wiring board 70, be provided with and connecting the power supply connector CN3 that connects the electric wire of usefulness to AC power AC, on the other end of the length direction of printed wiring board 70, be provided with a pair of load usefulness connector CN1, the CN2 that are electrically connected to and the lamp socket 81 (with reference to Figure 41) that mechanically be connected electric with discharge lamp La.In addition, from the above-mentioned end of printed wiring board 70 towards the above-mentioned other end, with rectification part DB, DC power supply portion 1, drive with integrated circuit 3, control arranged in order with integrated circuit 4 and switch portion 21, resonant structure 22, switch portion 21 and control are with integrated circuit 4 alignment arrangements on the short side direction of printed wiring board 70.In addition, the output capacitor C6 of DC power supply portion 1 is being installed on the printed wiring board 70 on the opposing face that the face that drives usefulness integrated circuit 3 and control usefulness integrated circuit 4 has been installed.

And then, in the example of Figure 38, the ground connection figure 71 that is located at current potential in the conductive pattern 71,72 on the printed wiring board 70, that be made as ground connection is observed from the thickness direction of printed wiring board 70, is configured in to drive with integrated circuit 3 and control with integrated circuit 4, and be connected between the high-pressure side figure 72 and switch portion 21 on the output of high-voltage side of DC power supply portion 1.In addition, in ground connection figure 71, connecting to drive and be branched to than the thin position, position that is connecting DC power supply portion 1, switch portion 21 and resonant structure 22 respectively with integrated circuit 3 and the position controlled with integrated circuit 4, on this thin position, be respectively equipped with a part of respectively and driving integrated circuit 3 and control two overlapping loop 71a, 71b of integrated circuit 4 from the thickness direction observation of printed wiring board 70.Thus, do not compare with situation between integrated circuit 4 and the switch portion 21 or the situation that do not make the situation of ground connection figure 71 branches or loop 71a, 71b be not set with ground connection figure 71 being observed to be configured in to drive with integrated circuit 3 and control from the thickness direction of printed wiring board 70 as shown in Figure 39, can reduce radiated noise that switch portion 21 produces and the conducted noise of in ground connection figure 71, propagating and give driving with integrated circuit 3 and control the influence that brings with integrated circuit 4 and improve noise tolerance.In addition, for the inhibition of common-mode noise, preferred above-mentioned ground connection figure 71 is via capacitive impedance ground connection.

Printed wiring board 70 as described above is accommodated in the housing 73 such shown in Figure 40 (a)～Figure 40 (c).Here, the signal shown in Figure 40 (a) input is used for the connection of the such sensor external of the lightness transducer 63 of execution mode 3 etc. with connector CN4.

And then above-mentioned housing 73 is taken in and is remained in the appliance body shown in Figure 41 80 and constitutes ligthing paraphernalia 8.The appliance body 80 of Figure 41 is mounted in the ligthing paraphernalia 8 of the so-called Fuji type that uses on the ceiling, is the triangular prism shape on the whole, is keeping the lamp socket 81 of the connection usefulness of discharge lamp La on the both ends of length direction respectively.In addition, make the outer surface of appliance body 80 for for example white, with light luminous intensity distribution to discharge lamp La.In addition, under the situation that (or be preferably the expose) transducer that need expose is set, be used for making that transducer exposes that to expose hole 80a just passable as the lightness transducer 63 of enforcement mode 3 as long as like that suitably be provided with as shown in figure 42.

(execution mode 13)

Below, utilize accompanying drawing that the supply unit of relevant embodiments of the present invention 3 is described.In addition, in the present embodiment, as described later, load circuit 302 constitutes by being the converter portion 320 of high frequency voltage from the dc voltage conversion of DC power supply circuit 301 and being applied in from the high frequency voltage of converter portion 320 and by resonance effect resonant structure 321 that discharge lamp La lights a lamp etc. is constituted, be used for discharge lamp La is supplied with the electric power of lighting a lamp, but load circuit 302 is not limited to this structure, it also can be the structure of the load (for example so long as lighting source is just passable, light-emitting diode etc.) beyond the discharge lamp La being supplied with action electric power.

Present embodiment as shown in figure 43, by will be from the ac voltage rectifier that exchanges power supply AC and the rectification circuit DB that constitutes by diode bridge of output ripple voltage, in the future the pulsating voltage of self-rectifying circuit DB boosts and smoothing and the DC power supply circuit 301 of output dc voltage, to be high frequency voltage from the dc voltage conversion of DC power supply circuit 301 and high frequency voltage is applied to discharge lamp La goes up the load circuit 302 that discharge lamp La is lit a lamp, the converter control circuit 306 of the converter described later portion 320 of control DC power supply control circuit 305 of DC power supply circuit 301 and control load circuit 302 is formed in the control circuit 303 that forms on the same semiconductor substrate, and the action initialization circuit 304 that is used for setting the action of control circuit 303 constitutes.

DC power supply circuit 301 is the boost choppers that are made of inductor L301, switch element Q301, diode D301, smoothing capacitor C301, thereby boost by the pulsating voltage according to the conducting that comes diverter switch element Q301 from the drive signal of DC power supply control circuit 305 described later/disconnection self-rectifying circuit DB in future, the direct voltage that will carry out smoothing to the pulsating voltage that boosts supplies in the load circuit 302.In addition,, be provided with the input voltage test section 310 of the input voltage that is used for detecting DC power supply circuit 301,, be provided with the output voltage test section 311 of the output voltage that is used for detecting DC power supply circuit 301 at outlet side at the input side of DC power supply circuit 301.In addition, switch element Q301 is made of MOSFET, and its gate terminal is connected via resistance R 301 on the described later the 301st the drive division 350.In addition, connecting resistance R 302 on the source terminal of switch element Q301, the falling quantity of voltages of resistance R 302 is input in the non-counter-rotating input terminal of the 2nd operational amplifier OP302 described later via the filter section 355 that is made of resistance R 305 and capacitor C307.By this filter section 355, the influence switch element Q301 of the peak current when preventing to switch to conducting because of switch element Q301 switches to disconnection.In addition, input voltage test section 310 and output voltage test section 311 all constitute (input voltage test section 310 is with reference to Figure 47, and output voltage test section 311 is with reference to Figure 56) by resistance and capacitor, are known, so omit detailed explanation here.

Load circuit 302 is by constituting with the lower part: converter portion 320, have 1 couple of switch element Q302, Q303 being connected in series, by according to the conducting/disconnection of alternately switching these switch elements Q302, Q303, will from the dc voltage conversion of DC power supply circuit 301 high frequency voltage from the drive signal of converter control circuit 306 described later; Resonant structure 321 is made of capacitor C302, C303 and inductor L302, is applied in the high frequency voltage from converter portion 320, by resonance effect discharge lamp La is lit a lamp; Preheating part 322 is made of capacitor C304, C305, C306 and transformer T301, is applied in from the high frequency voltage of converter portion 320 and with discharge lamp La preheating; And control power supply generative circuit 323, be applied in high frequency voltage from converter portion 320, generate the 2nd control power Vcc 302 described later.In addition, switch element Q302, Q303 are made of MOSFET, are inserted with resistance R 303, R304 respectively between the gate terminal of each switch element Q302, Q303 and the 2nd drive division 360 described later.

Control circuit 303 is started the startup portion 330 of the 2nd control power Vcc 302 by the output voltage of accepting DC power supply circuit 301, control power supply comparing section 331 with the supply voltage comparison of supply voltage and the 3rd reference voltage source Vref303 described later of the 2nd control power Vcc 302, generate the 1st control power supply generating unit 332 of the 1st control power Vcc 301 according to the comparative result of control power supply comparing section 331, according to the 3rd control power supply generating unit 333 that generates the 3rd control power Vcc 303 from the output signal that stops execution portion 334 described later, and the execution portion that stops 334 that controls the action of the 1st drive division 350 and the 2nd drive division 360 according to the judged result that stops judging part 342 described later constitutes.

Action initialization circuit 304 is by constitute the sequential control portion 340 that carries out frequency setting described later portion 341 and stop the sequential control of judging part 342 by microcomputer, output is used for setting the switch element Q302 of converter portion 320, the frequency setting portion 341 of the frequency setting signal of the driving frequency of Q303, stop judging part 342 according to what the sequential control of sequential control portion 340 output made stop signal that the action of the 1st drive division 350 and the 2nd drive division 360 stops, and the cycle configuration part 343 of setting the clock cycle of action initialization circuit 304 constitutes.

The 1st drive division 350 of the drive signal that DC power supply control circuit 305 is switched conducting/disconnection of the switch element Q301 of DC power supply circuit 301 by output, become the zero current detection portion 351 of predetermined electric current value if flow through the electric current of inductor L301 via the secondary coiling of the inductor L301 of DC power supply circuit 301 with next output zero-signal, control the rest-set flip-flop 352 of the action of the 1st drive division 350, with the detection voltage of output voltage test section 311 and supply voltage the 1st operational amplifier OP301 relatively of the 1st reference voltage source Vref301, the multiplier 353 that the output voltage of the detection voltage of input voltage test section 310 and the 1st operational amplifier OP301 is multiplied each other, and the output voltage of falling quantity of voltages in the resistance R 302 of DC power supply circuit 301 and multiplier 353 the 2nd operational amplifier OP302 relatively constituted.In addition, if constitute that the electric current that flows through becomes more than the predetermined electric current value then the peak current detection portion that exports peak signal in switch element Q301 by the 1st operational amplifier OP301, the 2nd operational amplifier OP302 and multiplier 353.

Converter control circuit 306 constitutes the changeable frequency portion 361 of the variable frequency of drive signal by the 2nd drive division 360 of the drive signal output of alternately conducting/disconnection of switch element Q302, the Q303 of switching converter portion 320 and the frequency setting signal of exporting according to the frequency setting portion 341 from action initialization circuit 304.

Below, the action of present embodiment is described.At first, utilize Figure 44, Figure 45 that the action of control circuit 303 is described.If connect the power supply of present embodiment, then the output voltage of DC power supply circuit 301 is imported in the startup portion 330 of the load circuit 302 of back level and control circuit 303.Power supply rigidly connect logical after, the output voltage of DC power supply circuit 301 is with the alternating voltage of the AC power AC smooth voltage with smoothing capacitor C301 smoothing, by this smooth voltage via the withstand voltage resistance R 306 of height with electric current supply in the series circuit of diode D302 and Zener diode ZD301.Be input to by the voltage VG that will produce between the two ends of this series circuit in the gate terminal of the switch element Q304 that is made of the withstand voltage MOSFET of height, switch element Q304 switches to conducting, and the 2nd control power Vcc 302 starts.And, the 2nd control supply voltage of power Vcc 302 and detection voltage Va described later, Vb, Vc rise in time (with reference to Figure 45 (a), Figure 45 (b)).

Is to detect voltage Va, Vb, Vc (Va＞Vb＞Vc) with the supply voltage of the 2nd control power Vcc 302 by the series circuit dividing potential drop that is made of resistance R 307～R310.Va is input in the non-counter-rotating input terminal of the 4th operational amplifier OP304 that controls power supply comparing section 331 with detection voltage, compares with the supply voltage that is input to the 3rd reference voltage source Vref303 in the counter-rotating input terminal.With detecting voltage Vb, Vc, be input in the non-counter-rotating input terminal of the 3rd operational amplifier OP303 via the 1st multiplexer circuit MP301 with the 1 pair of transmission gate element that is transfused to each voltage.Output signal and the output signal that stops execution portion 334 described later of the 3rd operational amplifier OP303 are input among the OR element OR301 conducting/disconnection of the switch element Q305 that constitutes by MOSFET that the output signal control by OR element OR301 and the series circuit of diode D302 and Zener diode ZD301 are connected in parallel.In addition, power supply rigidly connect logical after, the output signal that stops execution portion 334 is L (low) level, so the only conducting/disconnection of the output signal control switch element Q305 by the 3rd operational amplifier OP303.

At the beginning of the 2nd control power Vcc 302 starts, to detect in the non-counter-rotating input terminal that voltage Vc is input to the 3rd operational amplifier OP303 by the 1st multiplexer circuit MP301, with the supply voltage that is input to the 2nd reference voltage source Vref302 in the counter-rotating input terminal relatively.And, if detect the supply voltage that voltage Vc reaches the 2nd reference voltage source Vref302, the then output signal of the 3rd operational amplifier OP303 counter-rotating is by the non-counter-rotating input terminal input detection voltage Vb of the 1st multiplexer circuit MP301 to the 3rd operational amplifier OP303.Simultaneously, be input in the gate terminal of switch element Q305 via OR element OR301 by output signal the 3rd operational amplifier OP303, switch element Q305 switches to conducting, and switch element Q304 switches to disconnection (with reference to Figure 45 (b), Figure 45 (c)).

Switch element Q304 switches to disconnection, and the supply voltage of the 2nd control power Vcc 302 and detection voltage Va, Vb, Vc descend thus.And, if detect the supply voltage that voltage Vb reaches the 2nd reference voltage source Vref302, the then output signal of the 3rd operational amplifier OP303 counter-rotating will be detected in the non-counter-rotating input terminal that voltage Vc is input to the 3rd operational amplifier OP303 once more by the 1st multiplexer circuit MP301.In addition, along with the counter-rotating of the output signal of the 3rd operational amplifier OP303, switch element Q305 switches to and disconnects and switch element Q304 switches to conducting.Thereby the supply voltage of the 2nd control power Vcc 302 and detection voltage Va, Vb, Vc transfer rising once more to.By carrying out above-mentioned action repeatedly, the grid voltage of switch element Q304 becomes conducting/disconnection like that repeatedly shown in Figure 45 (c).

In addition, the supply voltage of the 2nd control power Vcc 302 is imported in the collector terminal of the switch element Q307 that is made of bipolar transistor of the 1st control power supply generating unit 332.The Zener diode ZD302 that the 1st control power supply generating unit 332 is connected in series by the 1st constant current source Iref301 between switch element Q307, the collector terminal that is connected switch element Q307 and the base terminal, with the 1st constant current source Iref301 and constitute with the switch element Q306 that constitutes by MOSFET that Zener diode ZD302 is connected in parallel.In the gate terminal of switch element Q306, be transfused to the output signal of the 4th operational amplifier OP304 of control power supply comparing section 331.So, the supply voltage of the 2nd control power Vcc 302 rises, if detect the supply voltage that voltage Va surpasses the 3rd reference voltage source Vref303, then switch element Q307 switches to conducting, the 1st control power Vcc 301 rises, with power supply voltage supplying in the action initialization circuit 304 (with reference to Figure 45 (b), Figure 45 (d)).In addition, the supply voltage of the 3rd reference voltage source Vref303 equates with the supply voltage of the 2nd reference voltage source Vref302.

If rise through T1 specified time limit from the 1st control power Vcc 301, then, accept this H level signal and in the 3rd control power supply generating unit 333, generate the 3rd control power Vcc 303 (with reference to Figure 45 (g)) from stopping execution portion 334 output H (height) level signals (with reference to Figure 45 (e)).In addition, by supplying with the supply voltage of the 3rd control power Vcc 303, the action of the 1st drive division 350 of DC power supply control circuit 305 begins (with reference to Figure 45 (f)).In addition, the supply voltage of the 3rd control power Vcc 303 is also supplied in the converter control circuit 306, begin action with the timing identical with the 1st drive division 350.So the converter portion 320 of load circuit 302 begins action.In addition, narrate in the back about the details of action initialization circuit 304.

Converter portion 320 begins action, supplies with the supply voltage of the 2nd control power Vcc 302 thus from 323 pairs of control circuits of control power supply generative circuit 303.Therefore, detect the supply voltage that voltage Vb, Vc always surpass the 2nd reference voltage source Vref302, switch element Q304 keeps the state (with reference to Figure 45 (b), Figure 45 (c)) of disconnection.In addition, in the present embodiment, in order to keep the off-state of switch element Q304 reliably, conducting/disconnection that output signal by the 3rd operational amplifier OP303 and the output signal of execution portion 334 of stopping to be come control switch element Q304.Promptly, because stopping the output signal of execution portion 334 when the action of converter portion 320 always is the H level, even output signal the 3rd operational amplifier OP303 is reversed so the supply voltage of the 2nd control power Vcc 302 is low, also can keep the off-state of switch element Q304.

In addition, under the situation that the action of converter portion 320 stops, service voltage from control power supply generative circuit 323 is low, detect the supply voltage that voltage Vb is lower than the 2nd reference voltage source Vref302 thus, switch element Q304 carries out conducting/disconnection action (with reference to Figure 45 (b), Figure 45 (c)) once more repeatedly.This conducting/disconnection action is as long as the smooth voltage of exporting from DC power supply circuit 301 is that enough sizes are just proceeded.

In addition, control power supply generative circuit 323 is so long as can generate the structure of the 2nd control power Vcc 302 according to the switch motion of converter portion 320, be what kind of structure can, so long as the above supply voltage of 10V is just passable so that can drive each switch element Q301～Q303.

Then, utilize accompanying drawing that changeable frequency portion 361 is described.Changeable frequency portion 361 as shown in figure 46, by the constant-voltage circuit that constitutes by the 5th operational amplifier OP305, be connected on the lead-out terminal of the 5th operational amplifier OP305 by resistance R 311, the load impedance circuit that R312 constitutes, the 6th operational amplifier OP306 with the supply voltage that in non-counter-rotating input terminal, is transfused to the 4th reference voltage source Vref304, flow through the current mirroring circuit CM of the electric current of capacitor C309 according to flowing to Current Regulation in the load impedance circuit, by the 2nd multiplexer circuit MP302 with a pair of transmission gate element that is connected with the 5th reference voltage source Vref305 and the 6th reference voltage source Vref306 respectively and oscillating circuit that voltage ratio the 7th operational amplifier OP307 between the two ends of the output voltage of the 2nd multiplexer circuit MP302 and capacitor C309 is constituted, and generation is used for preventing the switch element Q302 of converter portion 320, generating unit 361a dead time of the dead time of Q303 conducting simultaneously constitutes.

In the non-counter-rotating input terminal of the 5th operational amplifier OP305, be transfused to from the frequency setting signal of frequency setting portion 341 outputs of action initialization circuit 304 via the filter circuit that constitutes by resistance R 313, R314, R315 and capacitor C308.Frequency setting signal for example is the square-wave signal of duty ratio with regulation such shown in Figure 47 (d), is transformed to the direct current signal corresponding to duty ratio in filter circuit.Here, because the lead-out terminal of the 5th operational amplifier OP305 is connected on the lead-out terminal of the 6th operational amplifier OP306 via resistance 4311, so by changing the duty ratio of frequency setting signal, flow to the size variation of the electric current the lead-out terminal of the 6th operational amplifier OP306 from the lead-out terminal of the 5th operational amplifier OP305.So,, can change electric current that flows through capacitor C309 and the driving frequency that changes drive signal by changing the duty ratio of frequency setting signal.

In addition, drive signal via dead time generating unit 361a be imported into respectively among the high side drive 360a of portion and the 360b of low side drive portion of the 2nd drive division 360, by conducting/disconnection of each drive division 360a, 360b control switch element Q302, Q303.

Then, utilize Figure 43 that DC power supply control circuit 305 is described.DC power supply control circuit 305 carries out by conducting/disconnection of diverter switch element Q301 repeatedly to the savings of the energy of inductor L301 and from the release of the energy of inductor L301, and switch element Q301 carries out to switching in from the timing of the release of the energy of inductor L301 of conducting.Therefore, in DC power supply control circuit 305, be provided with zero current detection portion 351 as shown in figure 43, in zero current detection portion 351, drop near the 0V timing by the secondary coiling voltage that detects inductor L301, judge from inductor L301 discharged the timing of energy, the electric current that promptly flows through inductor L301 becomes the timing below the predetermined electric current value.In zero current detection portion 351, if judgement has discharged energy from inductor L301, then the terminal that is provided with of rest-set flip-flop 352 is imported the H level signal, make switch element Q301 switch to conducting via the 1st drive division 350.In addition, narrate in the back about the details of zero current detection portion 351.

In addition, under the situation of switch element Q301 conducting, detect the electric current that flows through switch element Q301, with output voltage comparison in the 2nd operational amplifier OP302 of falling quantity of voltages in the resistance R 302 and multiplier 353 by resistance R 302.And, if the falling quantity of voltages in the resistance R 302 surpasses the output voltage of multiplier 353, promptly flows through the electric current of switch element Q301 above setting, then, make switch element Q301 switch to disconnection via the 1st drive division 350 to the reseting terminal input H level signal (peak signal) of rest-set flip-flop 352.In addition, the afore mentioned rules value be supply voltage by the output voltage of DC power supply circuit 301 being detected 311 detection voltage and reference voltage source Vref301 in the 1st operational amplifier OP1 relatively and carry out FEEDBACK CONTROL and determine.

Below, utilize time diagram shown in Figure 47 that the sequential control of present embodiment is described.With the filament of preheating discharge lamp La in advance between warming up period, utilize for discharge lamp La is started resonance effect to discharge lamp La apply between the high-tension starting period, make discharge lamp La with the light output of hope light a lamp light a lamp during each during the processing of sequential control as in the past, carried out, utilize action initialization circuit 304 to carry out said sequence control in the present embodiment.

Shown in Figure 47 (a), if the 1st control power Vcc 301 rises and to action initialization circuit 304 supply line voltages, then becomes L level (with reference to Figure 47 (b)) to the input signal that stops execution portion 334 after the moment that the 1st control power Vcc 301 rises becomes the H level.And, before the output signal that stops execution portion 334 becomes the H level specified time limit T1 during in, the action of changeable frequency portion the 361, the 1st drive division the 350, the 2nd drive division 360 stops.

Here, controlled power Vcc 301 supply line voltages if constitute the microcomputer of action initialization circuit 304 from the 1st, then predefined initial start-up routine action carries out the function of microcomputer terminal and distribute, but has the impedance of terminal to become infinitely-great situation this moment.So, in the present embodiment, between the 1st control power Vcc 301 and the lead-out terminal that stops judging part 42, be connected resistance R 316, the output that prevents the microcomputer terminal instability that becomes.

If through T1 during the afore mentioned rules, then shown in Figure 47 (c), become the H level from the stop signal that stops execution portion 334, the action of changeable frequency portion the 361, the 1st drive division the 350, the 2nd drive division 360 begins, the driving frequency action of converter portion 320 to be set by frequency setting portion 341.Here, from the frequency setting signal of frequency setting portion 341 output shown in Figure 47 (d), from the moment t1 of the action of beginning converter portion 320 to moment t2 in advance starting period warming up period, from moment t2 to moment t3, constantly t3 later light a lamp during change duty ratio respectively.Therefore, the output signal of the 5th operational amplifier OP305 changes shown in Figure 47 (e) like that along with the variation of the duty ratio of frequency setting signal.Thereby, driving frequency in advance between warming up period for frequency f 1, between the starting period in for frequency f 2, lighting a lamp during in change (with reference to Figure 47 (f)) successively for frequency f 3.So, discharge lamp La through in advance between warming up period, between the starting period and light a lamp.

Here, the time constant of the filter circuit that is made of resistance R 313, R314, R315 and capacitor C308 that is located at the input prime of the 5th operational amplifier OP305 is made as the output voltage that makes filter circuit specified time limit T1 during in stable, the output voltage stabilization (with reference to Figure 47 (e)) of the 5th operational amplifier OP305 when in advance beginning between warming up period thus therefore can make the driving frequency stabilisation.

In addition, in advance between warming up period and between the starting period if by 304 decisions of action initialization circuit just can, generally need only just passable by the built-in oscillator or the timer circuit timing that are assembled in the microcomputer.In addition, in the present embodiment, decide the routine processes speed of microcomputer based on the clock cycle of setting by cycle configuration part 343 described later.

In addition, is 0% from the duty ratio of the frequency setting signal of frequency setting portion 341 output in advance between warming up period, just begin to improve duty ratio between the starting period after the action of converter portion 320 is stable, so can reduce the action of converter portion 320 after just having begun control circuit 303 and the current sinking in the action initialization circuit 304, make supply stabilisation from the supply voltage of each control power supply.And then, by when the action that makes converter portion 320 stops, being made as H level (soon being made as the H level) from the stop signal that stops judging part 342 to the input signal that stops execution portion 334, electric current is not flow in the resistance R 316, the current sinking in the control circuit 300 the when action that can reduce converter portion 320 stops.In addition, do not use the diadic of A/D translation circuit and D/A translation circuit H level/L level to handle, can significantly reduce the current sinking in the microcomputer by the input/output signal of microcomputer that will constitute action initialization circuit 304.In the case, the stress of the switch element Q304 of startup portion 330 is also significantly reduced, so can make 330 miniaturizations of startup portion.

Then, utilize accompanying drawing to describe to stopping execution portion 334.Stop execution portion 334 as shown in figure 48, by the detection voltage that is transfused to input voltage test section 310 and from the stop signal input part 334a of the stop signal voltage that stops judging part 342, accept from the output signal of stop signal input part 334a and the dwell time timing 334b of portion of time timing that the action that makes changeable frequency portion the 361, the 1st drive division the 350, the 2nd drive division 360 is stopped constitutes.

Stop signal input part 334a is transfused to the 8th operational amplifier OP308 of the detection voltage of input voltage test section 310 in the input terminal by the supply voltage that is transfused to the 7th reference voltage source Vref307 in non-counter-rotating input terminal and in counter-rotating, in non-counter-rotating input terminal, be transfused to from the stop signal voltage that stops judging part 342 and in counter-rotating and be transfused to the 9th operational amplifier OP309 of the supply voltage of the 7th reference voltage source Vref307 in the input terminal, and be transfused to each operational amplifier OP308, the OR element OR302 of the output signal of OP309 constitutes.

The dwell time timing 334b of portion is by the switch element Q308 that constitutes by MOSFET and be transfused in gate terminal from the output signal of stop signal input part 334a, be connected the capacitor C310 on the drain terminal of switch element Q308, the 2nd constant current source Iref302 to capacitor C310 supplying electric current, the 10th operational amplifier OP310 that is transfused to voltage between the two ends of capacitor C310 and is transfused to the supply voltage of the 8th reference voltage source Vref308 in non-counter-rotating input terminal in the counter-rotating input terminal constitutes.Switch element Q308 is according to the output signal switched conductive/disconnection from stop signal input part 334a, under the situation that switch element Q308 disconnects, capacitor C310 is charged by the charging interval of the static capacity decision of electric current that flows out from the 2nd constant current source Iref302 and capacitor C310.

Here, if the detection voltage of the 8th operational amplifier OP308 input voltage test section 310 surpasses assigned voltage (supply voltage of the 8th reference voltage source Vref308) then exports the H level signal.On the other hand, the 9th operational amplifier OP309 exports the L level signal under the situation that from the stop signal that stops judging part 342 is the L level, is output H level signal under the situation of H level.Thereby only the detection voltage at input voltage test section 310 is to be under the situation of L level below the assigned voltage and from the stop signal that stops judging part 342, and switch element Q308 switches to disconnection and capacitor C310 is charged.And, if the charging voltage of capacitor C310 surpasses assigned voltage (supply voltage of the 8th reference voltage source Vref308), then from the 10th operational amplifier OP310 output H level signal, generate the 3rd control power Vcc 303 as described above in the 3rd control power supply generating unit 333, the action of changeable frequency portion the 361, the 1st drive division the 350, the 2nd drive division 360 begins.That is, the charging interval of above-mentioned capacitor C310 is T1 during the afore mentioned rules, and the action of converter portion 320 stops in this period.

Below, utilize the elemental motion of flowchart text action initialization circuit 304 shown in Figure 49.At first, if from the 1st control power Vcc 301 supply line voltages (connecting the 1st control power Vcc 301), (S301), initial setting (S302) is carried out in then initial start-up routine action, and cycle configuration part 343 begins action (S303).The clock signal that will be generated by this cycle configuration part 343 is used as the fundamental clock of the microcomputer that constitute action initialization circuit 304, suitably switches in the present embodiment to come life cycle TA, TB (two clock signals of TA＞TB).The cycle of clock signal is short more, and the current sinking in the microcomputer increases more, so the clock signal of life cycle TA at first here.

Then, the information of duty ratio of the frequency setting signal of storage is in advance read (S304), set the frequency setting signal (S305) of output.Then, pick up counting (S306), the judgement (S307) during moving based on the time of timing.Promptly, go ahead of the rest between warming up period if reach moment t1 then be judged as, and the setpoint frequency setting signal is so that driving frequency becomes frequency f 1 (S309), if reach constantly t2 then be judged as between the starting period, and the setpoint frequency setting signal is so that driving frequency becomes frequency f 2 (S310), if reached constantly t3 would be judged as light a lamp during, and the setpoint frequency setting signal is so that driving frequency becomes frequency f 3 (S312).In addition, from start action initialization circuit 304 till the moment t1 specified time limit T1 during, the action of converter portion 320 is stopped (S308).

In addition, in the present embodiment, though do not illustrate, but be provided with the unusual known in the past abnormal detection circuit whether detection has normally been installed discharge lamp La and whether reached life-span etc. of discharge lamp La in addition, in above-mentioned action, in abnormal detection circuit, detect the action of control circuit 303 is stopped.Under the situation of the life tests of carrying out discharge lamp La like this, life tests is moved immediately in especially need be during the lighting a lamp of discharge lamp La.

So, transfer to light a lamp during the time, the cycle with clock signal in cycle configuration part 343 switches to period T B (S311).By like this cycle of clock signal being switched to the period T B shorter, even make the thirty years of age life tests action that accelerate of the processing speed of microcomputer than period T A.In addition, in the time of during the timing of switching this cycle is not limited to transfer to as described above and lights a lamp, during till during also can from beginning between warming up period to transferring to, lighting a lamp in advance, promptly stably supplying with the supply voltage of the 2nd control power Vcc 302 as long as begin the action of converter portion 320 from controlling 323 pairs of control circuits 303 of power supply generative circuit, is what kind of regularly can.

In addition, when the action of control circuit 303 being stopped detecting unusual as described above, in the cycle of clock signal is under the situation of period T B, by in cycle configuration part 343 cycle of clock signal being switched to period T A, reduces the current sinking in the action initialization circuit 304.So, can reduce to act on the stress in the startup portion 330, when restarting, the action that makes converter portion 320 can make supply stabilisation from the supply voltage of each control power supply.

Then, utilize accompanying drawing that zero current detection portion 351 is described.Zero current detection portion 351 makes the shielding part 351a that the output from the zero-signal of zero current detection portion 351 stops and accepting the output signal of the 11st operational amplifier OP311 and only produce 1 ono shot pulse generating unit 351b with pulse of any amplitude and constitute as shown in figure 50 by the secondary coiling voltage that is transfused to inductor L301 in counter-rotating in the input terminal and in being transfused between the 11st operational amplifier OP311 of the supply voltage of the 9th reference voltage source Vref309, specified time limit after the savings energy of inductor L301 discharges in non-counter-rotating input terminal.In addition, be provided with OR element OR303 between the terminal, in the input terminal of this OR element OR303, be transfused to the output signal of zero current detection portion 351 being provided with of zero current detection portion 351 and rest-set flip-flop 352.In addition, in another input terminal of OR element OR303, be transfused to the output signal of the portion that begins again 354.

Begin timing opening time of 354 couples of switch element Q301 of portion again, if and should surpass specified time limit (for example about 100 μ s) opening time, then by OR element OR303 is imported the H level signal, come the terminal that is provided with of rest-set flip-flop 352 is imported the H level signal, switch element Q301 is switched to conducting via the 1st drive division 350.In addition, ono shot pulse generating unit 351b and to begin portion 354 again be known in the past is so omit detailed explanation here.

Shielding part 351a is by the output signal that is transfused to the 11st operational amplifier OP311 and via the AND element AND301 of the output signal of the ono shot pulse generating unit 351b of NOT element NOT301, in gate terminal, be transfused to the switch element Q309 that constitutes by MOSFET of the output signal of AND element AND301, be connected the capacitor C311 on the drain terminal of switch element Q309, the 3rd constant current source Iref303 to capacitor C311 supplying electric current, in non-counter-rotating input terminal, be transfused to voltage between the two ends of capacitor C311 and in the counter-rotating input terminal, be transfused to the 12nd operational amplifier OP312 of the supply voltage of the 10th reference voltage source Vref310, and the AND element AND302 that is transfused to the output signal of the output signal of the 12nd operational amplifier OP312 and ono shot pulse generating unit 351b constitutes.

Below, utilize Figure 51 that the action of zero current detection portion 351 is described.At first, under the state that switch element Q301 disconnects, the supply voltage that if the savings energy of inductor L301 discharges, promptly if the secondary coiling voltage of inductor L301 is lower than the 9th reference voltage source Vref309, then from the 11st operational amplifier OP311 output H level signal, and from ono shot pulse generating unit 351b output ono shot pulse (with reference to Figure 51 (c), Figure 51 (d), Figure 51 (f)).

Usually, in the off period of switch element Q301, because switch element Q309 is an off-state, so capacitor C311 is charged by the 3rd constant current source Iref303, because charging voltage has surpassed the 10th reference voltage source Vref310, so from the 12nd operational amplifier OP312 output H level signal.So, by the output signal of the 12nd operational amplifier OP312 and the ono shot pulse of ono shot pulse generating unit 351b, the output signal of AND element AND1 becomes the H level, be transfused to the H level signal in the terminal being provided with of rest-set flip-flop 352, make switch element Q301 switch to conducting (with reference to Figure 51 (a)) via the 1st drive division 350.In addition, after the ono shot pulse from ono shot pulse generating unit 351b produced, switch element Q309 switched to conducting, so capacitor C311 discharge (with reference to Figure 51 (e)).

If switch element Q301 switches to conducting, the electric current that then flows through switch element Q301 increases and rises to the input voltage of the 2nd operational amplifier OP302.And, if this input voltage surpasses setting (output voltage of multiplier 353), then input H level signal in the reseting terminal of rest-set flip-flop 352 makes switch element Q301 switch to disconnection (with reference to Figure 51 (a), Figure 51 (b)) via the 1st drive division 350.If switch element Q301 switches to disconnection, then the secondary of inductor L301 coiling voltage transfers rising (with reference to Figure 51 (c)) to.And, if secondary coiling voltage surpasses the supply voltage of the 9th reference voltage source Vref309, then from the 11st operational amplifier OP311 output L level signal, switch element Q309 switches to disconnection, the charging (with reference to Figure 51 (d), Figure 51 (e)) of beginning capacitor C311.

The charging voltage of this capacitor C311 needs T2 specified time limit till reaching the supply voltage of the 10th reference voltage source Vref310, this specified time limit T2 during in from the 12nd operational amplifier OP312 output H level signal.Thereby, specified time limit T2 during in, the output signal of AND element AND2 always is the L level, so the output signal of the 11st operational amplifier OP311 is the H level in this period, even produce ono shot pulse, the terminal that is provided with of rest-set flip-flop 352 is not exported the H level signal from ono shot pulse generating unit 351b yet.So, shielding part 351a after switch element Q301 is switched to disconnection specified time limit T2 during in, the zero-signal (H level signal) from zero current detection portion 351 is stopped.

Here, as described in the invention problem that will solve, under the situation of the temporary decline of output voltage of AC power AC, even switch element Q301 switches to conducting, the also sufficient energy of savings in inductor L301.Therefore, if under the inadequate state of savings of the energy of inductor L301 switch element Q301 is being switched to disconnection, the energy of then putting aside in inductor L301 is insufficient, so the energy of savings is by abrupt release.Detect this situation and switch element Q301 is switched to conducting by zero current detection portion 351, switch element Q301 carries out conducting/disconnection repeatedly with the very short cycle, and switch element Q301 might be heated and damage.

So, in the present embodiment, by shielding part 351a is set as described above, in inductor L301, do not put aside under the situation of sufficient energy in the temporary decline of the output voltage of alternating voltage AC, specified time limit T2 during in, make from the action of zero current detection portion 351 output zero-signals to stop, preventing that switch element Q301 moment from switching to conducting.So, in the output voltage of AC power AC, taken place under the unusual situation, can prevent switch element Q301 with very short cycle switched conductive/disconnection, can prevent the cause thermal damage of the switch element Q301 that the increase of switching losses causes.Therefore, can realize the higher device of the less reliability of fault.

(execution mode 14)

Below, describe with reference to the supply unit of accompanying drawing relevant embodiments of the present invention 14.But the basic structure and the execution mode 13 of present embodiment are common, so give identical label and omit explanation for common part.Present embodiment is characterized in that shown in Figure 52, and ono shot pulse generating unit 351b, AND element AND301, NOT element NOT301 are not set in zero current detection portion 351.And, the output signal of the 11st operational amplifier OP311 is directly inputted in the AND element 302, and the output signal of rest-set flip-flop 352 is input in the gate terminal of switch element Q309.

In addition, in execution mode 13, be provided with filter section 355, but between the lead-out terminal of the 2nd operational amplifier OP302 and rest-set flip-flop 352, be provided with filter section 355 in the present embodiment in the input prime of the 2nd operational amplifier OP302.And then, the filter section 355 of present embodiment shown in Figure 53, by in gate terminal via NOT element NOT302 be transfused to the output signal of the 2nd operational amplifier OP302 the switch element Q310 that constitutes by MOSFET, be connected switch element Q310 drain terminal on capacitor C312 and the 4th constant current source Iref304 of capacitor C312 supplying electric current constituted.

In filter section 355, if the output signal of the 2nd operational amplifier OP302 is a H level then switch element Q310 switches to disconnection, the charging of beginning capacitor C312.And,, then, make switch element Q301 switch to disconnection via the 1st drive division 350 to the reseting terminal input H level signal of rest-set flip-flop 352 if the charging voltage of capacitor C312 surpasses assigned voltage.Here, will be made as Tf during the filtering from the time that reaches assigned voltage that is charged to of beginning capacitor C312.In addition, during the filtering Tf by the static capacity decision of electric current that flows out from the 3rd constant current source Iref303 and capacitor C312.

Below, utilize Figure 54 that the action of the zero current detection portion 351 of present embodiment is described.At first, under the state of switch element Q301 for disconnection, the supply voltage that if the savings energy of inductor L301 discharges, promptly if the secondary coiling voltage of inductor L301 is lower than the 9th reference voltage source Vref309, then from the 11st operational amplifier OP311 output H level signal (with reference to Figure 54 (c), Figure 54 (d)).Usually, in the off period of switch element Q301, because switch element Q309 is an off-state, so capacitor C311 is charged by the 3rd constant current source Iref303, because charging voltage surpasses the 10th reference voltage source Vref310, so from the 12nd operational amplifier OP312 output H level signal.So, make the output signal of AND element AND1 become the H level by the output signal of the 11st operational amplifier OP311 and the output signal of the 12nd operational amplifier OP312, the terminal that is provided with to rest-set flip-flop 352 is imported the H level signal, via the 1st drive division 350 switch element Q301 is switched to conducting (with reference to Figure 54 (a)).

If switch element Q301 switches to conducting, the electric current that then flows through switch element Q301 increases and rises to the input voltage of the 2nd operational amplifier OP302.And, if this input voltage surpasses setting (output voltage of multiplier 353), then behind Tf during the above-mentioned filtering of process, reseting terminal input H level signal to rest-set flip-flop 352 makes switch element Q301 switch to disconnection (with reference to Figure 54 (a), Figure 54 (b)) via the 1st drive division 350.If switch element Q301 switches to disconnection, then the output signal of rest-set flip-flop 352 becomes the L level, so switch element Q309 switches to disconnection, and the charging (with reference to Figure 54 (e)) of beginning capacitor C311.

Charging voltage and the execution mode 13 of this capacitor C311 are same, need T2 specified time limit till the supply voltage that arrives the 10th reference voltage source Vref310.So, shielding part 351a after switch element Q301 is switched to disconnection specified time limit T2 during in, the zero-signal (H level) from zero current detection portion 351 is stopped.

In addition, to the input voltage of the 2nd operational amplifier OP302 from the charging of beginning capacitor C311 through becoming 0V (with reference to Figure 54 (b)) time of delay after the Toff.This time of delay Toff be drive signal from the output of the 1st drive division 350 become the L level the time be carved into the actual delay that switches to disconnection of switch element Q301 and cause.

In addition, problem can not take place especially, but under the situation of Tf during the above-mentioned filtering than Toff weak point time of delay problem might take place under the situation of Tf during the above-mentioned filtering than Toff length time of delay.Promptly, the H level signal by the 2nd operational amplifier OP302 resets input to rest-set flip-flop 352 after, become the timing of L level in the drive signal of the 1st drive division 350 output, the grid current of switch element Q301 is superimposed in the input signal of the 2nd operational amplifier OP302.If the secondary coiling voltage at this moment inductor L301 does not switch to positive voltage, then the momentary reset input is disengaged, and trembles in switch element Q301, might apply excessive stress to switch element Q301.

In order to prevent this situation, ono shot pulse generating unit 351b generally is set as enforcement mode 13, generate ono shot pulse in the d/d timing of the savings energy of inductor L301, use this ono shot pulse that switch element Q301 is switched to conducting.But,, the circuit structure complicated problems that becomes is arranged then if use ono shot pulse generating unit 351b.

So, in the present embodiment, T2 specified time limit of shielding part 351a is set at longer than Tf during the filtering.Therefore, even the grid current of switch element Q301 is superimposed in the input signal of the 2nd operational amplifier OP302 as described above since this regularly during T2 specified time limit in, so do not have and capacitor C311 fully can be charged.Thereby, do not export the H level signal from the 12nd operational amplifier OP312, specified time limit T2 during in the output signal of AND element AND2 always be the L level, so can to rest-set flip-flop 352 terminal input H level signal is set, can prevent from switch element Q301, to tremble.

So, in the present embodiment, do not need ono shot pulse generating unit 351b is set as enforcement mode 13, so circuit structure is oversimplified, can realize that fault is still less and the higher device of reliability.

(execution mode 15)

Below, utilize accompanying drawing that the supply unit of relevant embodiments of the present invention 15 is described.But the basic structure and the execution mode 13 or 14 of present embodiment are common, so give identical label and omit explanation for common position.In addition, the control circuit 303 of present embodiment is formed in DC power supply control circuit 305, startup portion 330, control power supply comparing section the 331, the 1st control power supply generating unit the 332, the 3rd control power supply generating unit 333 on the same semiconductor substrate and forms.

Present embodiment possesses the low judging part 356 of the voltage whether output voltage that is located in the DC power supply control circuit 305 and judges DC power supply circuit 301 is lower than the low-voltage of the low regulation of assigned voltage than hope size (below be called " target voltage ") shown in Figure 55, detect the life tests circuit 307 in the life-span of discharge lamp La, the 1st unusual judging part 344 that is located in the action initialization circuit 304 and the action of DC power supply control circuit 305 and converter control circuit 306 is stopped based on the testing result of life tests circuit 307, and the 2nd unusual judging part 345 that is located in the action initialization circuit 304 and the action of DC power supply control circuit 305 and converter control circuit 306 is stopped based on the judged result of the low judging part 356 of voltage.In addition, just passable as long as life tests circuit 307 can detect the life-span of discharge lamp La, be known in the past, so omit detailed explanation here.In addition, in order to ensure the startability of discharge lamp La, in the 1st unusual judging part 345, do not carrying out unusual judgment processing between warming up period and between the starting period in advance.

The low judging part 356 of voltage is transfused to the 13rd operational amplifier OP313 of the reference voltage of the 11st reference voltage source Vref311 in the input terminal by the detection voltage that is transfused to output voltage test section 311 in non-counter-rotating input terminal and in counter-rotating, switch element Q311 that is made of MOSFET and the drain terminal that is inserted in switch element Q311 that is transfused to the output signal of the 13rd operational amplifier OP313 in gate terminal constitutes with the 3rd resistance R of controlling between the power supply generating unit 333 17 shown in Figure 56.

In the low judging part 356 of voltage, detect the low-voltage of the regulation lower and be judged as unusually than target voltage, judged result is sent to the 2nd unusual judging part 345.Particularly, the detection voltage of output voltage test section 311 and the supply voltage of the 11st reference voltage source Vref311 are compared in the 13rd operational amplifier OP313, if voltage is lower than the supply voltage of the 11st reference voltage source Vref311, promptly the output voltage of DC power supply circuit 301 becomes the low-voltage of the regulation lower than target voltage if detect, then from the 13rd operational amplifier OP313 output L level signal.And, make switch element Q311 switch to disconnection by this L level signal, by exporting the H level signals via 317 pairs the 2nd unusual judging parts 345 of resistance R, be judged as unusual from the 3rd control power supply generating unit 333.

In addition, as long as the supply voltage of the 11st reference voltage source Vref311 is than just can the supply voltage of the 1st reference voltage source Vref301 of the target voltage decision of the output voltage of DC power supply circuit 301 is low.For example, the target voltage of the output voltage of DC power supply circuit 301 is that the supply voltage of 400V, the 1st reference voltage source Vref301 is 2.5V, 80% the situation that drops to desired value at the output voltage with DC power supply circuit 301 is judged as under the unusual situation, and the supply voltage of the 11st reference voltage source Vref311 is 2.0V.

Below, utilize accompanying drawing that the action of low judging part 356 of voltage and the 2nd unusual judging part 345 is described.At first, if the output voltage of DC power supply circuit 301 is low, the detection voltage of output voltage test section 311 is lower than the supply voltage of the 11st reference voltage source Vref311, then the output signal of the 13rd operational amplifier OP313 becomes the L level, to the 2nd unusual judging part 345 input H level signals (with reference to Figure 57 (a), Figure 57 (b), Figure 57 (c)).In the 2nd unusual judging part 345, in DC power supply circuit 301, taken place unusually if be transfused to the H level signal then judge, control to transfer to the zero hour (with reference to Figure 57 (d), Figure 57 (e)) between the starting period during light a lamp.

And, be lower than at the output voltage of DC power supply circuit 301 regulation low-voltage during (corresponding to T3 specified time limit) between than the starting period under the short situation, the 2nd unusual judging part 345 control with from transfer between the starting period light a lamp during.Like this, through between the starting period, go out, also, do not kept so the sudden strain of a muscle of discharge lamp La is gone out as long as the output voltage of DC power supply circuit 301 recovers just discharge lamp La to be applied sufficient starting resistor even discharge lamp La dodges by in a single day.

On the other hand, the output voltage of DC power supply circuit 301 be lower than regulation low-voltage during (corresponding to T4 specified time limit.For example about 0.5 second) surpass under the situation between the starting period (with reference to Figure 58 (a), Figure 58 (b), Figure 58 (c)), the 2nd unusual judging part 345 is being exported stop signals from stopping judging part 342 after between the starting period, the action of the 1st drive division 350 and the 2nd drive division 360 is stopped, keeping halted state (with reference to Figure 58 (d), Figure 58 (e), Figure 58 (f)).Promptly, judgement in the input voltage of DC power supply circuit 301, exist permanent unusual or in load circuit 302, taken place to surpass DC power supply circuit 301 designed capacity power consumption or detect that fault etc. has taken place in 311 the parts is not recover immediately unusual constituting output voltage, but might reach the fault that can not guarantee fail safe, the action of DC power supply control circuit 305 and converter control circuit 306 is stopped, keeping halted state.

Below, utilize Figure 59 that the unusual judgment processing in the action initialization circuit 304 is described.At first, transfer to light a lamp during, the setpoint frequency setting signal is so that driving frequency becomes frequency f 3 (S401).Then, the output signal of the low judging part 356 of voltage is input in the 2nd unusual judging part 345 (S402), and the output signal of life tests circuit 307 is input in the 1st unusual judging part 344 (S403).In addition, be input in the 2nd unusual judging part 345 after also can being input in the 1st unusual judging part 344 earlier.Then, at first in the 2nd unusual judging part 345, carry out unusual judgment processing (S404), only in this unusual judgement, do not have under the unusual situation, in the 1st unusual judging part 344, carry out unusual judgment processing (S405).

Here, present embodiment is if approach the homophase action of the resonance frequency of resonant structure 321, and then idle current is less, thus can reduce circuit loss, but the sudden strain of a muscle of the discharge lamp La that lowly causes that the output voltage of DC power supply circuit 301 takes place is easily gone out.In the case, if the life-span with discharge lamp La is judged, promptly the unusual judgment processing of the 1st unusual judging part 344 serves as preferential, then the mistake that knocks out of discharge lamp La can be judged as discharge lamp La and reach the life-span, may keep the problem that stops of the action of DC power supply control circuit 305 and converter control circuit 306.

So, by serving as preferential with the unusual judgment processing of the 2nd unusual judging part 345 as described above, can prevent to be judged as in the mistiming that knocks out of discharge lamp La that discharge lamp La has reached the life-span, the situation that stops of keeping the action of DC power supply control circuit 305 and converter control circuit 306 takes place.

If in the unusual judgment processing of the 2nd unusual judging part 345, be judged as " having unusual ", then to transfer to (S406) between the starting period, the setpoint frequency setting signal is so that driving frequency becomes frequency f 2 (S407).Then, to being equivalent to the time timing (S408) between the starting period, then to the output signal (S409) of the low judging part 356 of the 2nd unusual judging part 345 input voltages.At this constantly, in the unusual judgment processing (S410) of the 2nd unusual judging part 345, be judged as under the situation of " no abnormal ", transfer to light a lamp during, the setpoint frequency setting signal is so that driving frequency becomes frequency f 3.On the other hand, under the situation that is judged as " having unusual ", make the action of DC power supply control circuit 305 and converter control circuit 306 stop (S411).

As mentioned above, under the temporary low situation of the output voltage of DC power supply circuit 301, make temporary the transferring between the starting period of action of DC power supply control circuit 305 and converter control circuit 306, in addition, surpass specified time limit and under the low situation at the output voltage of DC power supply circuit 301, be judged as be not to recover immediately unusual but might reach the fault that can not guarantee fail safe, can keep the stopping of action of DC power supply control circuit 305 and converter control circuit 306, so can improve the fail safe of device.

(execution mode 16)

Below, utilize accompanying drawing that the supply unit of relevant embodiments of the present invention 16 is described.But the basic structure and the execution mode 14 or 15 of present embodiment are common, so give identical label and omit explanation for common position.Present embodiment possesses the output voltage that is located in the DC power supply control circuit 305 and judges DC power supply circuit 301 and whether surpasses 1st regulation superpotential voltage rising judging part 357, life tests circuit 307 and the 1st unusual judging part 344 higher than target voltage shown in Figure 60.In addition, life tests circuit 307 and the 1st unusual judging part 344 are structures same with execution mode 15.

Voltage rising judging part 357 is shown in Figure 61, by the 3rd multiplexer circuit MP303 with a pair of transmission gate element that is connected with the 12nd reference voltage source Vref312 and the 13rd reference voltage source Vref313 respectively and be transfused to the detection voltage of output voltage test section 311 and constitute at the 14th operational amplifier OP314 that counter-rotating is transfused to the output signal of the 3rd multiplexer circuit MP303 in the input terminal in non-counter-rotating input terminal.In addition, the supply voltage of the 13rd reference voltage source Vref313 (the 1st regulation overvoltage) is bigger than the supply voltage (the 2nd regulation overvoltage) of the 12nd reference voltage source Vref312.The output signal of the 14th operational amplifier OP314 is imported in the reseting terminal of rest-set flip-flop 352 and is imported in the input terminal of OR element OR304.In addition, be transfused to the output signal of rest-set flip-flop 352 in another input terminal of OR element OR304, the output signal of OR element OR304 is imported in the portion that begins again 354.

Become the L level then pick up counting if begin the output signal of the 354 OR element OR304 of portion again, if the time of timing surpasses Tr then export H level signal specified time limit.And, by this H level signal is input to being provided with in the terminal of rest-set flip-flop 352 via OR element OR303, make switch element Q301 switch to conducting via the 1st drive division 350 thus, restart the action of DC power supply control circuit 305.

Below, utilize Figure 62 that the action of voltage rising judging part 357 is described.In voltage rising judging part 357, be judged as unusually if detect than the 1st high regulation overvoltage of target voltage, the action of DC power supply control circuit 305 is stopped.Particularly, the detection voltage of output voltage test section 311 and the supply voltage of the 13rd reference voltage source Vref313 are compared in the 14th operational amplifier OP314, if detect the supply voltage that voltage surpasses the 13rd reference voltage source Vref313, then from the 14th operational amplifier OP314 output H level signal.And, this H level signal is input in the reseting terminal of rest-set flip-flop 352, make switch element Q301 switch to disconnection via the 1st drive division 350, the action of DC power supply control circuit 305 stops (with reference to Figure 62 (a), Figure 62 (b), Figure 62 (c)).

Here, the output voltage of the 3rd multiplexer circuit MP303 is to be the supply voltage of the 13rd reference voltage source Vref313 under the situation of L level in the output signal of the 14th operational amplifier OP314, if but the output signal of the 14th operational amplifier OP314 be the H level, promptly if the output voltage of DC power supply circuit 301 becomes the 1st regulation overvoltage higher than target voltage, then the output voltage of the 3rd multiplexer circuit MP303 is switched to the supply voltage of the 12nd reference voltage source Vref312.And, along with the action of DC power supply control circuit 305 stops, the output voltage of DC power supply circuit 301 descends, if the detection voltage of output voltage test section 311 is lower than the supply voltage of the 12nd reference voltage source Vref312, i.e. the 2nd regulation overvoltage, then the output signal of the 14th operational amplifier OP314 becomes L level (with reference to Figure 62 (b)).At this constantly, because the output signal of rest-set flip-flop 352 also is the L level,, in beginning portion 354 again, pick up counting so the output signal of OR element OR304 is the L level.And,, then, restart the action (with reference to Figure 62 (c), Figure 62 (d)) of DC power supply control circuit 305 by this H level signal from beginning portion's 354 output H level signals again if the time of timing surpasses Tr specified time limit.

In the past, surpassed at the output voltage of DC power supply circuit 301 under the superpotential situation of regulation the action of DC power supply control circuit 305 is stopped, if surpass Tr then control specified time limit by the time that begins portion's 354 timing again to restart.In the case, need imagination during beginning portion 354 again, to set Tr specified time limit (for example 100～200 μ s) to the steady needed time of output voltage from the action that stops DC power supply control circuit 305.This specified time limit, Tr was because by the capacitor volume decision that is located on the chip that constitutes the portion that begins again 354, so for specified time limit Tr set longly and have to make capacitor volume to become big, have chip area to increase and begin the problem that portion 354 maximizes again.

So, in the present embodiment, as mentioned above, in voltage rising judging part 357, when the action of DC power supply control circuit 305, with the detection voltage ratio of the supply voltage of the 13rd reference voltage source Vref313 and output voltage test section 311, judge whether the output voltage of DC power supply circuit 301 has surpassed the 1st regulation overvoltage higher than target voltage.And, when the action of DC power supply control circuit 305 stops, with the detection voltage ratio of the supply voltage of the 12nd reference voltage source Vref312 and output voltage test section 311, judge whether the output voltage of DC power supply circuit 301 has dropped near the target voltage.

So, when the action of DC power supply control circuit 305 stops, as long as just passable by beginning 354 timing Tr specified time limit of portion again, can significantly shorten Tr specified time limit so compare by the situation in the past that begins portion's 354 timing again when action from DC power supply control circuit 305 stops near the moment that output voltage drops to the target voltage.Thereby the capacitor volume of setting Tr specified time limit is less just enough, makes the portion that begins again 354 miniaturizations so can reduce chip area.

As mentioned above, can make circuit miniaturization in the present embodiment and realize the still less higher supply unit of reliability of fault.In addition, also can make up the structure of low judging part the 356, the 2nd unusual judging part 345 of voltage of record in the execution mode 16 in the present embodiment.In the case, can realize the still less higher supply unit of fail safe of fault.

And then present embodiment possesses the preheating part 20 that is used for when the startup of discharge lamp La each filament of discharge lamp La being distinguished preheating.Preheating part 20 possess have an end be connected on the tie point of switch element Q10, Q20 of power converter portion 2 via capacitor C6 and the once coiling of other end ground connection and respectively and the series circuit of capacitor C4, C5 be connected the transformer Tr1 of two secondaries coilings between the two ends of each filament of discharge lamp La.

And then present embodiment possesses each switch element Q10, Q12 of power converter portion 2 is connected via resistance R 1, R2 respectively and disconnect each switch element Q10, Q12 of driving electric transformation component 2 and control from the sequential control portion 41 of the frequency of the alternating electromotive force of 2 pairs of discharge lamp La outputs of power converter portion from the frequency that 2 couples of discharge lamp La of power converter portion supply with the drive division 31 of alternating electromotive force and the action by controlling and driving portion 31 by conducting.

Drive division 31 is located at the driving that is made of high-withstand-voltage integrated circuit (HVIC) and uses in the integrated circuit 3, and sequential control portion 41 is located at the control that is made of the integrated circuit that is called microcontroller (microcomputer) and uses in the integrated circuit 4.As control integrated circuit 4, do not comprise the structure of A/D converter and D/A converter as long as use the magnitude of voltage of input and output to have only two grades, just can suppress to control consumption electric power preferably with in the integrated circuit 4.

In addition, present embodiment possesses the driving power portion 5 that is exported from power converter portion 2 supply capabilities as the direct current power that drives the power supply of using integrated circuit 3 after the action of drive division 31 begins.Driving power portion 5 has outlet side capacitor (not shown) and is connected on the tie point of switch element Q10, Q20 of power converter portion 2 and with the charging circuit (not shown) of outlet side capacitor charging, with the both end voltage of outlet side capacitor as output voltage.Under the action from drive division 31 began both end voltage stable status through time enough and outlet side capacitor, the both end voltage of outlet side capacitor was that the output voltage of driving power portion 5 is for example 10V.

And then, driving with in the integrated circuit 3, be respectively equipped with the action of drive division 31 begins before by export from DC power supply portion 1 supply capability as the startup portion 32 of the direct current power of the power supply of driving power portion 5 and by from driving power portion 5 supply capabilities and more than the output voltage of driving power portion 5 is the reference voltage of regulation during generate to supply to the direct current power of for example 5V of the power supply of integrated circuit 4 and control the control power supply unit of using in the integrated circuit 4 33 as control.

If explain, then as shown in Figure 3, startup portion 32 has that an end is connected on the output of high-voltage side of DC power supply portion 1 and the other end is connected the impedance component Z1 on the output of driving power portion 5 via the 1st switch element Q101.That is, during the 1st switch element Q101 conducting of startup portion 32 in, the output voltage V dc of DC power supply portion 1 is exported to driving power portion 5 via impedance component Z1 and the 1st switch element Q101, thus with the output capacitor charging of driving power portion 5.Above-mentioned the 1st switch element Q101 is made of the high withstand voltage field-effect transistor of n type raceway groove, the grid of the 1st switch element Q101 is connected on the tie point of DC power supply portion 1 and impedance component Z1 via resistance R 101, and the parallel circuits ground connection of the 2nd switch element Q102 that constitutes via the series circuit of diode D101 and Zener diode ZD2 and field-effect transistor by the n raceway groove.In addition, startup portion 32 has respectively 4 divider resistances with the output voltage of driving power portion 5 (below be called " driving voltage ") Vcc2 dividing potential drop, from the tie point of these divider resistances respectively different 3 kinds of output voltage (voltage ratio) detect voltage Va, Vb, Vc.And then startup portion 32 possesses in counter-rotating and is transfused to comparator C P1 on the 1st reference voltage Vr1 of regulation and lead-out terminal is connected the 2nd switch element Q102 via logic and circuit OR1 the grid in the input terminal.In the non-counter-rotating input terminal of comparator C P1, be transfused to detection voltage Vb, Vc via the multiplexer TG1 that uses transmission gate circuit to constitute.Above-mentioned multiplexer TG1 is connected on the lead-out terminal of comparator C P1, in during the output H level that constitutes at comparator C P1 the 2nd low detection voltage (below be called " the 2nd detects voltage ") Vb is input in the non-counter-rotating input terminal of comparator C P1, in during the output L of comparator C P1 level, Vc is input in the non-counter-rotating input terminal of comparator C P1 with minimum detection voltage (below be called " the 3rd detect voltage ").

Use Fig. 4 that the action of startup portion 32 is described.After power supply just is switched on, output by comparator C P1 is the L level, detect voltage Vc with the 3rd and be input in the non-counter-rotating input terminal of comparator C P1, and by the 2nd switch element Q102 is disconnected, by the Zener voltage of Zener diode ZD2 with the 1st switch element Q101 conducting.During the 1st switch element Q101 conducting, the outlet side capacitor of driving power portion 5 is recharged by the output power that impedance component Z1 and the 1st switch element Q101 via startup portion 32 are supplied to DC power supply portion 1, and driving voltage Vcc2 rises gradually thus.Reach the 1st reference voltage Vr1 if the final the 3rd detects voltage Vc, then the output of comparator C P1 becomes the H level.So, input voltage to non-counter-rotating input terminal is changed to the 2nd detection voltage Vb higher than the 3rd detection voltage Vc, and the 2nd switch element Q102 is switched on and the 1st switch element Q101 is disconnected, and is stopped to the supply of the electric power of driving power portion 5 from startup portion 32 thus.Also do not begin the action of drive division 31 in this moment, not from 2 pairs of driving power portion 5 supply capabilities of power converter portion, so the discharge by output capacitor, driving voltage Vcc2 begins to descend.Reach the 1st reference voltage Vr1 if the final the 2nd detects voltage Vb, then the output of comparator C P1 becomes the L level once more, the output voltage of driving power portion 5 begins to rise, if then the 3rd detection voltage Vc reaches the 1st reference voltage Vr1, then the output of comparator C P1 becomes the H level once more.Then, supply with such direct current power shown in Fig. 4 (a) from DC power supply portion 1, and shown in Fig. 4 (e) from stop execution portion 34 (aftermentioned) during the input L level of logic and circuit OR1 and drive division 31 stop, by carrying out repeatedly of above-mentioned action, the grid voltage of the 1st switch element Q101 changes shown in Fig. 4 (c) like that, driving voltage Vcc2 is shown in Fig. 4 (b), and detecting voltage Vc the 3rd becomes the such upper voltage limit of the 1st reference voltage Vr1, and the 2nd detect voltage Vb and become between the such lower voltage limit of the 1st reference voltage Vr1 and change up and down repeatedly.

Here, driving, be provided with the execution portion 34 that stops of controlling and driving portion 31 and startup portion 32 respectively with in the integrated circuit 3.The output that stops execution portion 34 is imported among logic and the circuit OR1, in during stopping the output L level of execution portion 34 drive division 31 stopped and will supply with conducting to the electric power of driving power portion 5 from startup portion 32, but in during stopping the output H level of execution portion 34, by irrelevant with the output of comparator C P1 and disconnect and to supply with disconnection from startup portion 32 to the electric power of driving power portion 5 with the 2nd switch element Q102 conducting and with the 1st switch element Q101.Wherein, during stopping the output H level of execution portion 34 in, undertaken supplying with to the electric power of driving power portion 5 by drive division 31 action (promptly generating the output of the driving usefulness of switch element Q10, Q20 such shown in Fig. 4 (f)) from power converter portion 2.

In addition, driving with in the integrated circuit 3, be provided with by from driving power portion 5 supply capabilities and more than the output voltage of driving power portion 5 is the reference voltage of regulation during generate as control with the direct current power of the assigned voltage of the power supply of integrated circuit 4 (below be called " control voltage ") Vcc1 and control is used the control power supply unit 33 of integrated circuit 4 supplies.If explain, then control the comparator C P2 that power supply unit 33 possesses the highest detection voltage in the detection voltage that the divider resistance that is transfused to startup portion 32 in non-counter-rotating input terminal exports (below be called " the 1st detects voltage ") Va and be transfused to the 1st reference voltage Vr1 in the counter-rotating input terminal, be connected the series circuit of the output of driving power portion 5 and constant current circuit Ir1 between the earthing potential and Zener diode ZD3, base stage is connected on the tie point of constant current circuit Ir1 and Zener diode ZD3 and collector electrode is connected on the output of driving power portion 5 and emitter is connected the transistor Q103 of control with the npn type on the integrated circuit 4 as the output of control power supply unit 33, and be connected in that the field-effect transistor by n type raceway groove on the Zener diode ZD3 constitutes in parallel and grid is connected switch element Q104 on the lead-out terminal of comparator C P2.Promptly, shown in Fig. 4 (d), constitute like that, control voltage vccs 1 to control with integrated circuit 4 outputs in only during the 1st detection voltage Va is above the 1st reference voltage Vr1, the 1st detect voltage Va be lower than the 1st reference voltage Vr1 during in do not export control voltage vcc 1 (output voltage of promptly controlling power supply unit 33 is roughly 0), the driving voltage that the 1st detects voltage Va when being the 1st reference voltage Vr1 is a said reference voltage.Here, control the circuit of voltage vccs 1 via noise removing electricity consumption container C 51 ground connection from driving with integrated circuit 4 outputs with 3 pairs of controls of integrated circuit.

In addition, driving with in the integrated circuit 3, be provided with the oscillating portion 35 of the square wave of the output frequency corresponding with the output of sequential control portion 41, drive division 31 disconnects switch element Q10, the Q20 of control power converter portion 2 with the frequency conducting of the output of oscillating portion 35.And then, driving with in the integrated circuit 3, be provided with and stopped 34 controls of execution portion and the report voltage vcc 3 of output regulation and the driving power portion 30 that in the action of drive division 31, output stopped in the action of drive division 31.The same circuit structure of power supply unit 33 for example can be made and control in driving power portion 30.Report voltage vcc 3 is reported the operate condition of drive division 31 also to controlling with integrated circuit 4 outputs for control being used integrated circuit 4.In addition, oscillating portion 35 with above-mentioned report voltage vcc 3 as power supply.That is, stopping execution portion 34 stops to make oscillating portion 35 and drive division 31 to stop respectively by making from report power supply unit 30 to the electric power supply of oscillating portion 35.

Oscillating portion 35 possesses that non-counter-rotating input terminal is connected in the sequential control portion 41 via resistance R 103 and lead-out terminal is connected on the counter-rotating input terminal and via two resistance R 106 with the parallel circuits ground connection of control electricity consumption container C 103 via resistance R 104 as shown in Figure 5, R102 ground connection and counter-rotating input terminal are connected the voltage follower OP1 that is made of operational amplifier on the lead-out terminal, and in non-counter-rotating input terminal, be transfused to the 2nd reference voltage Vr2 of regulation and the input terminal that reverses is connected the control operational amplifier OP2 on the lead-out terminal of voltage follower OP1 via resistance R 106.The lead-out terminal of this operational amplifier 102 is connected on the grid of charging with switch element Qc, this charging is connected in the charging that is transfused to report voltage vcc 3 in each input respectively with between output of current mirroring circuit CM1 and the resistance R 102 with switch element Qc, above-mentioned charging with another output of current mirroring circuit CM1 via vibration electricity consumption container C 102 ground connection.In addition, oscillating portion 35 possesses in an input and to be connected the 1st discharge that charging constitutes with the field-effect transistor by p type raceway groove on the above-mentioned output of current mirroring circuit CM1 via grid and to be transfused to switch element Qd and to report voltage vcc 3 and connecting on another input and vibrate electricity consumption container C 102 and each output is distinguished the discharge current mirroring circuit CM2 of ground connection.And then oscillating portion 35 possesses a side the comparator C P3 that the counter-rotating input terminal is connected on the vibration electricity consumption container C 102 and is transfused to the 4th reference voltage Vr4 of the low regulation of the 3rd reference voltage Vr3 of regulation and Bi Di 3 reference voltage Vr3 via the multiplexer TG2 that uses transmission gate circuit to constitute in non-counter-rotating input terminal.The lead-out terminal that on above-mentioned multiplexer TG2, is connecting comparator C P3, in during the output H level that constitutes at comparator C P3 the 3rd reference voltage Vr3 is input in the non-counter-rotating input terminal of comparator C P3, the 4th reference voltage Vr4 is input in the non-counter-rotating input terminal of comparator C P3 in during the output L of comparator C P3 level.In addition, use on the current mirroring circuit CM2 in discharge, the 2nd discharge switch element Q105 that is being connected in parallel, the 2nd discharge is made of the field-effect transistor of n type raceway groove with switch element Q105, and grid is connected on the lead-out terminal of comparator C P3.

Action to oscillating portion 35 describes.Do not have under the fully charged state in vibration electricity consumption container C 102, comparator C P3 is output as the H level, thus, is transfused to the 3rd reference voltage Vr3 in the non-counter-rotating input terminal of comparator C P3, with switch element Q105 conducting.During this period, use the conducting of switch element Q105 with the 2nd discharge on the current mirroring circuit CM2 by being connected in discharge in parallel, be suppressed via the discharge of discharge with the vibration electricity consumption container C 102 of current mirroring circuit CM2, by use the charging of current mirroring circuit CM1 via charging, the both end voltage of vibration electricity consumption container C 102 rises gradually.The both end voltage of electricity consumption container C 102 reaches the 3rd reference voltage Vr3 if finally vibrate, then the output of comparator C P3 becomes the L level, input voltage to the non-counter-rotating input terminal of comparator C P3 becomes the 4th reference voltage Vr4, and the 2nd discharge disconnects with switch element Q105.So, becoming than many with the charging current of current mirroring circuit CM1 via the discharging current of discharge via charging with current mirroring circuit CM2, the both end voltage of the electricity consumption container C 102 of vibrating thus is low gradually.And if the both end voltage of vibration electricity consumption container C 102 reaches the 4th reference voltage Vr4, then the output of comparator C P3 becomes the H level once more, below repeats same action.Thus, the both end voltage of vibration electricity consumption container C 102 promptly changes up and down between the 3rd reference voltage Vr3 and the 4th reference voltage Vr4 shown in Fig. 6 (a) like that repeatedly to the input voltage of the counter-rotating input terminal of comparator C P3, and the output of comparator C P3 becomes such square wave shown in Fig. 6 (b) .And then oscillating portion 35 has the output Shaping circuit 35a that the output Shaping of comparator C P3 is exported to drive division 31. output Shaping circuit 35a have shown in Fig. 6 (c) like that the 1st rectangular signal generating unit (not shown) that generates the 1st rectangular signal by the output of comparator C P3 being carried out two divided-frequency for example, generation is with the 2nd rectangular signal generating unit (not shown) of the 2nd rectangular signal of the output counter-rotating of the 1st rectangular signal, and td dead time of the constant time lag of the conducting (counter-rotating from the L level to the H level) by making the 1st rectangular signal regulation generates shown in Fig. 6 (d) the such the 1st timing that drives signal and the conducting by making the 2nd rectangular signal and above-mentioned same delay and generates the 2nd and drive signal and drive signal and the 2nd with the 1st and drive signal and output to respectively generating unit dead time (not shown) the drive division 31. Drive division 31 has a switch element Q10 making power converter portion 2 conducting and at the off period of the 1st drive signal (L level during) the 1st drive division 31a that breaks and another switch element Q20 that makes power converter portion 2 conducting and the 2nd drive division 31b that breaks at the off period of the 2nd drive signal (L level during) in conduction period of the 2nd drive signal (H level during) in conduction period of the 1st drive signal (H level during) .That is, by above-mentioned dead time of generating unit, two switch element Q10, Q20 preventing power converter portion 2 are by the while conducting.In said structure, do not require extra high capability value for vibration electricity consumption container C 102, so vibration electricity consumption container C 102 can be in control with constituting in the integrated circuit 4.

Here, the charging current and the discharging current of vibration electricity consumption container C 102 are respectively: high more with the input voltage of the counter-rotating input terminal of operational amplifier OP2 to control, promptly to control the both end voltage of electricity consumption container C 103 high more then more little.That is, the frequency of above-mentioned the 1st drive signal and the 2nd drive signal, be drive division 31 action frequency and to the frequency of the alternating electromotive force of discharge lamp La output (below be called " operating frequency) be: the both end voltage of control electricity consumption container C 103 is high more then low more.

The time that control begins according to the supply from controlling voltage vcc 1 shown in Figure 64 (a) with the sequential control portion 41 of integrated circuit 4, the both end voltage of the control electricity consumption container C 103 shown in Figure 64 (e) is changed, thus after the preheating action t1～t2 that each filament of discharge lamp La is distinguished preheating, make the startup action t2～t3 of the beginning of lighting a lamp of discharge lamp La, then, transfer to the operating stably t3～t4 that lights a lamp that keeps discharge lamp La.For example, sequential control portion 41 is via the unit of pwm signal such shown in 103 pairs of control of resistance R electricity consumption container C, 103 output Figure 64 (d), makes the both end voltage variation of control electricity consumption container C 103 by the duty ratio of this pwm signal.Particularly, by in preheating action t1～t2, making the said PWM signal stop (in other words making above-mentioned duty ratio is 0), in operating stably t3～t4, improving above-mentioned duty ratio than starting action t2～t3, the both end voltage stage ground of control electricity consumption container C 103 is risen, promptly shown in Figure 64 (f), make the interim decline of operating frequency f1～f3.That is, making operating frequency be the highest operating frequency f1 in t1～t2 is moved in preheating, is than the low operating frequency f2 of preheating action t1～t2 in starting action t2～t3, is than starting lower operating frequency f3 among action t2～t3 in operating stably t3～t4.In addition, the output of sequential control portion 41 is not limited to pwm signal, so long as the signal that the both end voltage of control electricity consumption container C 103 is changed is just passable.Make operating frequency f1～f3 than between the two ends of the switch element Q20 of the downside that is connected power converter portion 2 and comprise the resonance frequency height of the resonant circuit of discharge lamp La, be that operating frequency f1～f3 is low more, from the electric power increase more of 2 pairs of discharge lamp La outputs of power converter portion.That is, by the stage decline of operating frequency f1 as described above～f3, to the interim increase of the output power of discharge lamp La.In addition, the timing t 3 that begins to start the timing t 2 of action t2～t3 and beginning operating stably t3～t4 is roughly necessarily the duration of preheating action t1～t2 and the duration that starts action t2～t3 respectively respectively for example by the timing decision.

In addition, stop execution portion 34 in the action that from the dwell time T1 that begins to stipulate with the output of the control voltage vcc 1 of integrated circuit 4 to control, does not begin drive division 31.Thereby the timing of beginning preheating action t1～t2 becomes from beginning after output the dwell time T1 through regulation of control with the control voltage vcc 1 of integrated circuit 4.Make the elongated degree of dwell time T1 to the sufficient discharge that can control electricity consumption container C 103, thereby, even operating stably t3～t4 is being stopped the situation that the back starts at once once more, also control the discharge of electricity consumption container C 103 among the dwell time T1 before the preheating action t1～t2 that begins then fully, so t1 does not have from power converter portion 2 to the excessive situation of the output power of discharge lamp La when the beginning of preheating action t1～t2.

Here,, be provided with to be connected and stop to stop control part 42 in the execution portion 34 with in the integrated circuit 4 in control.Be connected via resistance R 51 on the circuit of control voltage vcc 1 to the circuit that stops execution portion 34 that drives with integrated circuit 3 from the control part 42 that stops of control with integrated circuit 4.Stop control part 42 and usually the current potentials of foregoing circuit are made as the L level that equates with earthing potential, when drive division 31 is stopped, being made as and controlling the H level that voltage vcc 1 equates, indicate stopping of drive division 31 by current potential with foregoing circuit.That is, indicated drive division 31 stop during in above-mentioned resistance R 51, do not flow through electric current and do not consume electric power, and constitute the situation that in above-mentioned resistance R 51, always flows through the structure of electric current and compare and reduced consumption electric power.And, stop execution portion 34 and do not make drive division 31 actions in during stopping the output H level of control part 42.In the example of Figure 64, from begin to control voltage vcc 1 output to the end of operating stably t3～t4 the time t4 will be maintained the L level to the input that stops execution portion 34 (stopping the output of control part 42), thus from the output that begins to control voltage vcc 1 through dwell time T1 after beginning preheating action t1～t2, but becoming under the situation that the H level is changed to the L level then to the input that stops execution portion 34 after the output that begins to control voltage vcc 1, moving t1～t2 through beginning preheating after the dwell time T1 from become the L level to the input that stops execution portion 34.Promptly, strictly say be from control power supply unit 33 output control voltage vccs 1 and to the input that stops execution portion 34 be the L level state continuance moment of dwell time T1 begin preheating action t1～t2, from finishing operating stably t3～t4 to then beginning to guarantee stopping of dwell time T1 at least preheating action t1～t2.

And then present embodiment possesses output and the power supply test section 165 of direct voltage that the voltage of the output voltage smoothing of rectification part DB is corresponding and for example is made of the divider resistance with the output voltage dividing potential drop of DC power supply portion 1 and the high more DC power supply test section 167 of then exporting high more voltage of output voltage of DC power supply portion 1.

In addition, with in the integrated circuit 3, be provided with the circuit of the switch element Q1 that is used for driving DC power supply portion 1 in the driving of present embodiment.If explain, then driving, be provided with output and the 7th reference voltage Vr7 of regulation and the poor corresponding wrong amplifier OP4 of the output voltage of DC power supply test section 167 with in the integrated circuit 3, multiplier 36a with the output multiplication of the output of power supply test section 165 and wrong amplifier OP4, be transfused to comparator C P7 on the tie point of the output of multiplier 36a and switch element Q1 that non-counter-rotating input terminal is connected DC power supply portion 1 and resistance R 5 in the input terminal in counter-rotating, in reseting terminal, be transfused to the flip-flop circuit 36b of the output of comparator C P7, and go up and according to the output of flip-flop circuit 36b and conducting disconnects the 36c of power drives portion of the switch element Q1 that drives DC power supply portion 1 via the switch element Q1 that resistance R 4 is connected DC power supply portion 1.

And then, on the inductor L1 of DC power supply portion 1, being provided with 2 coilings of an end ground connection, the other end of these 2 times coilings is connected to be located at and drives with on the 36d of zero current detection portion in the integrated circuit 3.The 36d of zero current detection portion is connected being provided with on the terminal of flip-flop circuit 36c, based on exergonic the finishing of voltage detecting inductor L1 of induction in above-mentioned 2 coilings, the terminal input pulse is set to flip-flop circuit 36b when detecting exergonic the finishing of inductor L1.

Thus, with the periodically conducting disconnection driving of switch element Q1 of DC power supply portion 1, its duty ratio of FEEDBACK CONTROL is so that the output voltage of DC power supply portion 1 becomes the target voltage of regulation.This target voltage is to make the output voltage of DC power supply test section 167 become the voltage of the 7th reference voltage Vr7.

And then present embodiment possesses parameter that detection changes and the output life tests portion 63 corresponding to the voltage of detected parameter when the end of lifetime of discharge lamp La.Particularly, the asymmetrical current that produces detects as above-mentioned parameter in the life tests portion 63 of present embodiment in discharge lamp La, and output is corresponding to its voltage.

In addition, in control with in the integrated circuit 4, be provided with output based on life tests portion 63 judge whether be as discharge lamp La be end of lifetime abnormality the end of lifetime state and will be input to the discharge lamp judging part 43 that stops in the control part 42 corresponding to the output of judged result.That is, discharge lamp judging part 43 is the unusual judging parts of load-side in the technical scheme.

If explain, then as shown in figure 25, life tests portion 63 possess an end via the inductor L2 that the filament of resistance R 111 and discharge lamp La is connected power converter portion 2 go up, the capacitor C106 of other end ground connection and the parallel circuits of resistance R 113.In addition, capacitor C106 is connected on the life-span judging part 43 via the diode D103 that makes negative electrode towards capacitor C106, and the tie point of this diode D103 and life-span judging part 43 is connected on the output (control voltage vcc 1) of control power supply unit 33 via resistance R 112.

Here, at discharge lamp La is not under the situation of end of lifetime, in the lighting a lamp of discharge lamp La, Idc-mutually about equally to the electric current of power converter portion 2 (below be called " outflow electric current ") to the electric current of life tests portion 63 (below be called " inflow current ") Idc+ and from life tests portion 63 from power converter portion 2.Thus, the both end voltage of the capacitor C106 of life tests portion 63, be that the output voltage of life tests portion 63 is maintained roughly certain voltage (below be called " normal voltage "), this normal voltage is about control voltage vcc 1 usefulness resistance R112, R113 voltage after partial.In addition, the tie point of the inductor L2 of power converter portion 2 and discharge lamp La is connected via resistance R 114 on the output of high-voltage side of DC power supply portion 1.

On the other hand, if discharge lamp La becomes end of lifetime, then in each filament, produce difference by the consumption that in discharge lamp La, is coated in the radiation body on the filament, one of above-mentioned electric current I dc+, Idc-becomes than another big (promptly producing asymmetrical current), between the output voltage and above-mentioned normal voltage of life tests portion 63, poor corresponding to above-mentioned electric current I dc+, Idc-poor (size of asymmetrical current) taken place.For example, under the situation that outflow electric current I dc+ is Duoed than inflow current Idc-, the output voltage of life tests portion 63 becomes than above-mentioned normal voltage height, otherwise under the situation that outflow electric current I dc+ lacks than inflow current Idc-, the output voltage of life tests portion 63 becomes and forces down than above-mentioned normal electrical.

Life-span judging part 43 compares the output voltage of life tests portion 63 lower voltage limit with the regulation of forcing down than the high set upper limit voltage of normal voltage and than normal electrical respectively, if to be upper voltage limits following and more than the lower voltage limit then be judged as and be not the end of lifetime state for the output voltage of life tests portion 63, if the output voltage of life tests portion 63 surpasses upper voltage limit or is lower than lower voltage limit then is judged as the end of lifetime state.For example, be that 5V, normal voltage are under the situation of 2.5V at control voltage vcc 1, upper voltage limit is made as 4V and lower voltage limit is made as 1V.

And then, driving with in the integrated circuit 3, be provided with output based on DC power supply test section 167 and judge whether it is the abnormality (below be called " the low state of direct voltage ") of output voltage deficiency of DC power supply portion 1 and output the low judging part 37 of direct voltage corresponding to the voltage of judged result.That is, the low judging part 37 of direct voltage is the unusual judging parts of mains side in the technical scheme.If specifically describe, then the low judging part 37 of direct voltage possesses the output voltage that is transfused to DC power supply test section 167 in non-counter-rotating input terminal and be transfused to the comparator C P8 of the 8th reference voltage Vr8 of the regulation lower than the 7th reference voltage Vr7 and the switch element Q107 that the FET by the n channel-type on the lead-out terminal that grid is connected this comparator C P8 constitutes in the counter-rotating input terminal as shown in figure 27.The end ground connection of this switch element Q107 and be transfused to report voltage vcc 3 via resistance R 32 in the other end, the tie point of this switch element Q107 and resistance R 32 is connected on the control usefulness integrated circuit 4 as the output of the low judging part 37 of direct voltage.Above-mentioned the 8th reference voltage Vr8 is made as corresponding to 50%～80% of the 7th reference voltage Vr7 of target voltage.Promptly, the low judging part 37 of direct voltage when the output voltage of DC power supply test section 167 be that the 8th reference voltage Vr8 is not judged as the low state of direct voltage when above and output is made as the L level, when the output voltage of DC power supply test section 167 is lower than the 8th reference voltage Vr8, be judged as the low state of direct voltage, output is made as the H level.For example, be under 80% the situation of the 7th reference voltage Vr7 making the 8th reference voltage Vr8, when about low state of direct voltage that is judged as 80% time of the output voltage fall short voltage of DC power supply portion 1.

In addition,, be provided with the output proper transformation of the low judging part 37 of direct voltage is input to the judgement input part 144 that stops in the control part 42 with in the integrated circuit 4 in control.

Present embodiment stop control part 42 at any time with reference to the output of life-span judging part 43 with judge the output of input part 144, if be judged as the end of lifetime state by life-span judging part 43, then be made as the H level to the output that drives with integrated circuit 3, drive division 31 grades that drive with integrated circuit 3 are stopped, and sequential control portion 41 is stopped.

In addition, stop control part 42 in that low judging part 37 is judged as under the situation of the low state of direct voltage by direct voltage, not that drive division 31 and sequential control portion 41 are stopped immediately, but control sequence control part 41 is restarted time T 5 (with reference to Figure 29) with what will start that action stipulates, if still be judged as the low state of direct voltage through after restarting time T 5, then constantly at this, same when being judged as the end of lifetime state, to be made as the H level to the output that drives with integrated circuit 3, drive division 31 grades that drive with integrated circuit 3 are stopped, and sequential control portion 41 is stopped.

The action of the present embodiment when expression is judged as the low state of electric current in Figure 28 and Figure 29.In Figure 28 and Figure 29, be that the time of the output voltage of (a) expression DC power supply test section 167 changes, the time of the output of the comparator C P8 of the low judging part 37 of (b) expression direct voltage changes, the time of the output of the low judging part 37 of (c) expression direct voltage changes, the time of the output of (d) order of representation control part 41 changes, the time of (e) expression operating frequency changes respectively, (f) expression stops control part 42 and change for the time that drives with the output of integrated circuit 3.In the example of Figure 28, finish in by the low state of direct voltage (being that the low judging part of direct voltage is the state of H level) than the time T 4 of restarting time T 5 weak points, do not stop to stop of control part 42 enforcements, beginning operating stably again through after restarting time T 5.In addition, Figure 29 represents that duration by the low state of direct voltage has reached and restarts time T 5, carried out stopping the action under the situation about stopping that control part 42 implements.In the present embodiment, the execution portion 34 that stops with integrated circuit 3 of driving is when stopping that the 36c of power drives portion is also stopped, in Figure 29, after the end of the startup action that has continued to restart time T 5, because the 36c of power drives portion stops, the output voltage of the output voltage of DC power supply portion 1 and DC power supply test section 167 descends.

In addition, make immediately when being judged as the low state of direct voltage under the situation that drive division 31 and the 36c of power drives portion stop, the low state of direct voltage for example because instantaneous power failure etc. cause, can not make discharge lamp La light a lamp even eliminated at short notice.

To this, in the present embodiment, restart time T 5 by when being judged as the low state of direct voltage, starting action as described above, under the situation that the low state discharge lamp of the direct voltage of short time as described above La sudden strain of a muscle is gone out, discharge lamp La is lit a lamp once more.In addition, under the situation that is judged as the low state of direct voltage after the end that above-mentioned startup of restarting time T 5 is moved, drive division 31 and the 36c of power drives portion are stopped, even, also can avoid by the FEEDBACK CONTROL of mistake the electric stress of overaction on circuit element or discharge lamp La so do not reflect that in for example output the output voltage of DC power supply portion 1 is always under the such situation of 0V because of fault DC power supply test sections 167 such as short circuits.

In addition, if the low state of direct voltage takes place, then consider simultaneous for example the sudden strain of a muscle of discharge lamp La go out and lamp current is temporary becomes asymmetric and mistake is judged as the end of lifetime state, if carry out stopping of drive division 31 and the 36c of power drives portion, then might can not carry out startup action in fact based on the judgement of the low state of direct voltage as described above by such erroneous judgement is disconnected.In addition, for example, operating frequency guarantees the so-called slow action of side mutually by fully being left with respect to the resonance frequency of the resonant circuit of power converter portion 2 and discharge lamp La formation, the erroneous judgement that can avoid sudden strain of a muscle as described above to go out causing is disconnected, if but like this, then increase and the circuit loss increase, so not preferred by idle current.

So, the control part 42 that stops of present embodiment is judging under both situation of end of lifetime state and the low state of direct voltage that the action with based on the judgement of the low state of direct voltage serve as preferentially, be judged as the low state of direct voltage during in do not carry out action corresponding to the judgement of end of lifetime state.Thus, can avoid when the sudden strain of a muscle of discharge lamp La is gone out, taking place because of the disconnected situation that drive division 31 grades are stopped of the erroneous judgement of end of lifetime state.

In addition, use in the integrated circuit 4 in the control of present embodiment, be provided with the clock portion 45 that generates as the clock signal of the periodic signal of telecommunication, the frequency of clock signal is high more, control increases more with the consumption electric power of integrated circuit 4, the responsiveness that stops control part 42 on the other hand is fast more, and is fast more for the response of unusual generation.In the present embodiment, being conceived to especially need be for the quick response that end of lifetime state and the low state of direct voltage take place in operating stably, clock portion 45 has adopted the clock frequency TB that makes among operating stably t3～t4 than the high structure of clock frequency TA in during other shown in Figure 64 g.Thus, guarantee higher response speed by in operating stably t3～t4, clock frequency being made as higher frequency TB, and in the stopping of drive division 31, clock frequency is made as lower frequency TA, reduce the electric stress that acts in the startup portion 32 by suppressing to consume electric power, can make driving voltage Vcc2 stable.Here, clock frequency is just passable as long as be made as higher frequency TB in operating stably t3～t4, the t3 when timing that clock frequency is switched to higher frequency TB from lower frequency TA is not limited to the beginning of the such operating stably t3～t4 of Figure 64 (g), also can be with the time from the beginning of preheating action t1～t2 t2 during to the beginning of operating stably t3～t4 other t3 regularly switch clock frequency.

In addition, also can constitute to be provided with sequential control portion has been carried out the count section (not shown) that starts the inferior counting number of action once more based on the judgement of the low state of direct voltage, reached set upper limit number of times (for example 5 times) even the back is judged as the low state of direct voltage at above-mentioned number of times by this count section counting, sequential control portion 41 does not begin to start action yet and stops control part 42 output is made as the H level, and drive division 31 grades are stopped.

In addition, load is not limited to discharge lamp La, so long as the device that the electric power of supply is increased gradually is just passable.

And then, also the 36d of zero current detection portion can be constituted shown in Figure 65 like that.If explain, then the 36d of zero current detection portion of Figure 65 possesses that secondary coiling that the counter-rotating input terminal is connected the inductor L1 of DC power supply portion 1 is gone up and the input comparator CP9 that is transfused to the 9th reference voltage Vr9 of regulation in non-counter-rotating input terminal, the single-shot trigger circuit OS of output that when the L level is reversed to the H level, begins the pulse of regulation amplitude when the output of input comparator CP9, the non-inverter circuit INV of the output of output single-shot trigger circuit OS, the 1st logic integrated circuit AND1 of the logic product of the output of the output NAND circuit INV of output input comparator CP9, by being the reservation electricity consumption container C 107 of the constant current source Ir3 charging of power supply with control voltage vcc 1, constitute and be connected in the switch element Q108 that keeps on the electricity consumption container C 107 and on grid, connecting the lead-out terminal of the 1st logic integrated circuit AND1 in parallel by the FET of n channel-type, in the counter-rotating input terminal, be transfused to the 10th reference voltage Vr10 of regulation and on non-counter-rotating input terminal, connecting the output comparator CP10 that keeps electricity consumption container C 107, and the 2nd logic integrated circuit AND2 that the logic product of the output of the output of output comparator CP10 and single-shot trigger circuit OS is exported as the output of the 36d of zero current detection portion.

Utilize Figure 31 that the action of the 36d of zero current detection portion of Figure 65 is described.Consider the situation that 2 coilings of the inductor L1 of DC power supply portion 1 change shown in (b) among Figure 31 like that to the input voltage of the 36d of zero current detection portion.So the output of input comparator CP9 becomes among Figure 31 such shown in (c), the output of single-shot trigger circuit OS becomes among Figure 31 such shown in (e).Keeping electricity consumption container C 107 is discharged sharp via switch element Q108 when the 1st logic integrated circuit AND1 is output as the H level, so during the output L of the 1st logic integrated circuit AND1 level, be during the output L level of input comparator CP9 and the output H level of single-shot trigger circuit OS during in be recharged, the output voltage to output comparator CP10 is risen gradually.Here, the 36d of zero current detection portion among Figure 31 shown in (g) be output as the H level during be during the output of single-shot trigger circuit OS is the output H level of H level and output comparator CP10, promptly in Figure 31 the output of the output comparator CP10 shown in (f) be reversed to from the H level output before tight, single-shot trigger circuit OS of L level the pulse duration amount during, thus, the output of the 36c of power drives portion becomes among Figure 31 output such shown in (a).As long as the output of output comparator CP10 is not the H level, the output of the 36d of zero current detection portion does not just become the H level, so after the input voltage to the 36d of zero current detection portion is lower than the 9th reference voltage Vr9, among the retention time T6 of the regulation before the both end voltage that keeps electricity consumption container C 107 has reached the 10th reference voltage Vr10, the output of the 36d of zero current detection portion does not become the H level.In other words, as long as to the input voltage of the 36d of zero current detection portion be lower than the 9th reference voltage Vr9 during duration do not reach above-mentioned retention time T6, the output of flip-flop circuit 36b does not just become the H level, thereby the switch element Q1 of DC power supply portion 1 is not switched on.

In addition, in DC power supply portion 1,, after switch element Q1 just has been switched on, flow among the detection resistance R3 from the electric current of output capacitor C6 (below be called " adverse current electric current ") by the contrary recovery time of spurious impedance and diode D1.In addition, driving, if descend from the voltage of AC power AC input (below be called " input supply voltage ") to the input voltage of the counter-rotating input terminal of the comparator C P7 on the reseting terminal that is connected flip-flop circuit 36b then descend with in the integrated circuit 3.And, become under the situation of H level in the output of input supply voltage with respect to the low and above-mentioned comparator C P7 of above-mentioned countercurrent electric rheology, although do not put aside energy fully in inductor L1, switch element Q1 also is disconnected.In the case, though can be disconnected once more with above-mentioned same switch element Q1, can expect repeatedly and switch element Q1 is switched on disconnection with the short cycle by this once more with switch element Q1 conducting in the very short time.If switch element Q1 is switched on disconnection with the short cycle like this, then the electric stress of overaction on switch element Q1.

With respect to this, in the structure of Figure 65, as mentioned above, as long as to the input voltage of the 36d of zero current detection portion be lower than the 9th reference voltage Vr9 during duration do not reach retention time T6, just not with the switch element Q1 conducting of DC power supply portion 1, the off-state that is switch element Q1 continues retention time T6 at least, even so near the situation that the input voltage of the 36d of zero current detection portion fine changes as the right-hand member of Figure 31 also can be avoided the conducting disconnection lost of life of the switch element Q4 of DC power supply portion 1 because of the short cycle.

And then, in the example of Figure 65, the output of the 36d of zero current detection portion is connected being provided with on the terminal of flip-flop circuit 36b via logic and circuit OR3, driving with in the integrated circuit 3, be provided with the output that monitors flip-flop circuit 36b and when being the L level more than the lasting stipulated time of the output of flip-flop circuit 36b (for example 100 μ second) via above-mentioned logic and circuit OR3 the 36e of the portion that begins again that the terminal input pulse is set to flip-flop circuit 36.

(execution mode 18)

The execution portion 34 that stops of present embodiment is shown in Figure 66, judge the low of input supply voltage based on the output of power supply test section 165, when being judged as input supply voltage when low, same when becoming the H level with the output that stops control part 42, output is made as the L level and drive division 31 and report power supply unit 30 are stopped.

If specifically describe, then power supply test section 165 is the unit that the direct voltage of capacitor smoothing is also used the output voltage of rectifier DB with the divider resistance dividing potential drop in output as shown in figure 20.In addition, stop that execution portion 34 possesses the 5th reference voltage Vr5 that is transfused to regulation in non-counter-rotating input terminal and the input comparator CP4 that in the counter-rotating input terminal, is transfused to the output voltage of power supply test section 165, non-counter-rotating input terminal is connected and stops on the control part 42 and be transfused to the input comparator CP5 of the 5th reference voltage Vr5 in the counter-rotating input terminal, export above-mentioned two input comparator CP4, the logic of the output of CP5 and logic and circuit OR2, the constant current source Ir2 of delay electricity consumption container C 105 chargings that drive the outside of using integrated circuit 3 will be located at, constitute and be connected the switch element Q106 that postpones on the electricity consumption container C 105 and in grid, be transfused to the output of logic and circuit OR2 side by side by the FET of n channel-type, and the output comparator CP6 that in the counter-rotating input terminal, is transfused to the 6th reference voltage Vr6 of regulation in connection delay electricity consumption container C 105 on the non-counter-rotating input terminal.This output comparator CP6 be output as the H level during during drive division 31 and the action of report power supply unit 30, be output report voltage vcc 3 during.

The above-mentioned action that stops execution portion 34 is described.Stopping execution portion 34 will be from the control voltage vcc 1 of control power supply unit 33 output as power supply, the charging that postpones electricity consumption container C 105 thus when starting begins to begin simultaneously with output from the control voltage vcc 1 of control power supply unit 33, when the both end voltage that postpones electricity consumption container C 105 has reached the 6th reference voltage Vr6, the output of output comparator CP6 becomes the H level, begin the action of drive division 31 and the output of report voltage vcc 3 thus, at this moment, in startup portion 32, switch element Q101 is fixed to off-state.That is, that the capability value that postpones electricity consumption container C 105 is consistent except that the charging interval T2 and the dwell time T1 that obtain with the output current of the constant current source Ir2 that stops execution portion 34 with the product of the 6th reference voltage Vr6.

In addition, be lower than under the situation of the 5th reference voltage Vr5 at the output voltage of power supply test section 165 or stopping under the situation that control part 42 is output as the H level, output by any input comparator CP4, CP5 becomes the H level and with switch element Q106 conducting, to postpone electricity consumption container C 105 via switch element Q106 discharges sharp, be lower than the 6th reference voltage Vr6 and the output of output comparator CP6 becomes the L level by the both end voltage that postpones electricity consumption container C 105, carry out stopping of drive division 31 and report voltage vcc 3.Here, time (below be called " the retention time ") T3 (with reference to Figure 21) that becomes the L level from the output that switch element Q106 is disconnected to output comparator CP6 becomes enough short.

An example of the action of expression present embodiment in Figure 21.In the example of Figure 21, become the moment of L level in the output that stops control part 42 shown in Figure 21 (a), output voltage by the power supply test section 165 shown in Figure 21 (b) is lower than the 5th reference voltage Vr5, the output of an input comparator CP4 shown in Figure 21 (c) is the H level, thereby the output of logic shown in Figure 21 (d) and circuit 2 also becomes the H level.If the output voltage of final power supply test section 165 surpasses the 5th reference voltage Vr5, then the output by logic and circuit OR2 becomes the L level and with switch element Q106 disconnection, begins to postpone the charging of electricity consumption container C 105.And then if through charging interval T2, the both end voltage that postpones electricity consumption container C 105 reaches the 6th reference voltage Vr6, and then the output of output comparator CP6 becomes the H level, the action of beginning drive division 31 and the output of the report voltage vcc 3 shown in Figure 21 (f).Then, if the output of power supply test section 165 descends and is lower than the 5th reference voltage Vr5, then the output of output comparator CP6 becomes the L level in very short retention time T3, here, the action of drive division 31 and the output of report voltage vcc 3 is stopped respectively.

In addition, in the present embodiment, shown in Figure 67, sequential control portion 41 make to the duty ratio of the pwm signal (Figure 67 (d)) of oscillating portion 35 output when t1 is to the end that starts action t2～t3 when the beginning of t1～t2 is moved in preheating t3 become big continuously gradually.Thus, the both end voltage of the control electricity consumption container C 103 shown in Figure 67 (e) becomes big with linearity among t1～t3 during above-mentioned, the operating frequency f3 of the operating frequency f1 of t1 to operating stably t3～t4 was with the linearity step-down when operating frequency shown in Figure 67 (f) was moved the beginning of t1～t2 from preheating.

(execution mode 19)

The structure of present embodiment and execution mode 2 are common, so give identical label and omit detailed diagram and explanation for common part.

In the present embodiment; shown in Figure 68; driving with in the integrated circuit 3, be provided with to judge whether it is the overvoltage condition that uprises unusually of the output voltage V dc of DC power supply portion 1 and the low overvoltage protection portion 39 of output voltage that when being judged as overvoltage condition, makes DC power supply portion 1.

In addition, in control with in the integrated circuit 4, be provided with to as the timing portion 46 of accumulative total timing service time of the accumulative total of the time of using supply unit, by nonvolatile memory constitute and at least power supply disconnect during in keep the storage part 47 of accumulative total service time and before the accumulative total by 46 timing of timing portion reaches time device lifetime as the regulation in life-span of supply unit service time, make being output as the L level and making the report portion 48 that is output as the H level after adding up service time to reach time device lifetime.With accumulative total service time for example be transfused to come self-driven report voltage vcc 3 with integrated circuit 3 during timing in (be drive division 31 move during).

And then, driving with in the integrated circuit 3, be provided with the report input part 38 of the output of input report portion 48.Report input part 38 is connected in the overvoltage protection portion 39, and overvoltage protection portion 39 changes action according to the output of report portion 48.

If explain, then as shown in figure 36, report input part 38 by the counter-rotating input terminal be connected the 11st reference voltage Vr11 that in the report portion 48 and in non-counter-rotating input terminal, is transfused to regulation, lead-out terminal is connected control via resistance R 33 and constitutes with the comparator C 11 on the counter-rotating input terminal of operational amplifier OP2.Make the 11st reference voltage Vr11 lower and than the magnitude of voltage height of the output of the L level of report portion 48 than the magnitude of voltage of the output of the H level of report portion 48.That is, report input part 38 is so-called inverter circuits, and the output of report input part 38 is the output counter-rotating that the output of above-mentioned comparator C 11 makes report portion 48.

Overvoltage protection portion 39 possess the output that in non-counter-rotating input terminal, is transfused to DC power supply test section 167 and in the counter-rotating input terminal, be transfused to regulation the 12nd reference voltage Vr12 comparator C P12 and the logic product of the output of this comparator C P12 and the output of report input part 38 is outputed to logic integrated circuit AND3 in the reseting terminal of flip-flop circuit 36b.Promptly; when totally not reaching the time device lifetime service time; when the output voltage of DC power supply test section 167 surpasses the 12nd reference voltage Vr12; carry out moving by the overvoltage protection that the switch element Q4 that disconnects control DC power supply portion 1 descends the output voltage V dc of DC power supply portion 1; after totally reaching device lifetime service time; output by report input part 38 becomes the L level and the output of logic integrated circuit AND3 is fixed as the L level, does not carry out above-mentioned overvoltage protection action.

According to said structure, after totally reaching time device lifetime,, on the switch element Q4 of DC power supply portion 1, act on higher electric stress easily by no longer carrying out the overvoltage protection action service time.Thereby, switch element Q4 uprises than the possibility that other voltage components reach the life-span more earlier, so countermeasure of the easy establishment known current fuse of use (not shown) etc., in addition, the timing of fault is inhomogeneous because switch element Q4 reaches the life-span, even, do not have the situation that discharge lamp La is turned off the light simultaneously when the life-span of these a plurality of supply units reaches so begin the situation of the use of a plurality of supply units simultaneously yet.

In addition; overvoltage protection portion 39 is not limited to the above; also can replace logic integrated circuit AND3 is set and for example constitute like that as shown in figure 37; the 13rd reference voltage Vr13 of the regulation that the 12nd reference voltage Vr12 and Bi Di 12 reference voltage Vr12 are high is input among the comparator C P12 via the multiplexer TG3 that uses transmission gate circuit to constitute respectively, will be input to the 13rd reference voltage Vr13 that voltage in the counter-rotating input terminal of comparator C P12 of overvoltage protection portion 39 is made as the regulation higher than the 12nd reference voltage Vr12 in during the output H of report portion 48 level.If adopt this structure; then the voltage in the counter-rotating input terminal of the comparator C P12 by being input to overvoltage protection portion 39 after accumulative total reaches the time device lifetime service time uprises; be difficult for carrying out the overvoltage protection action, can access same effect thus.

Claims (23)

1. discharge lamp ignition device is characterized in that possessing:

DC power supply portion, output DC power;

Resonant structure constitutes resonant circuit with discharge lamp;

Switch portion comprises 1 switch element at least, follows the conducting of this switch element to disconnect to switch being connected of DC power supply portion and resonant structure;

Drive division carries out conducting by the switch element to switch portion and disconnects driving, comes from resonant structure discharge lamp to be supplied with alternating electromotive force;

Control part, the frequency of the action by controlling and driving portion is controlled from the frequency of resonant structure to the alternating electromotive force of discharge lamp output;

Driving power portion begins the back by from the switch portion supply capability in the action of drive division, and output DC power;

Startup portion, before the action of drive division begins by from DC power supply portion supply capability, and to driving power portion supply capability; And

The control power supply unit, by from driving power portion supply capability, at the output voltage of driving power portion be more than the reference voltage of regulation during, generate as the direct current power of the power supply of control part and be supplied to control part;

To be operating frequency decide corresponding to the both end voltage of control with capacitor the frequency that drive division drives switch portion, and this control makes the both end voltage variation with capacitor corresponding to the output of control part;

When control part starts at discharge lamp, after each filament of discharge lamp is distinguished the preheating action of preheating, make the startup action of the beginning of lighting a lamp of discharge lamp, control is changed, with the both end voltage of capacitor to transfer to the operating stably of lighting a lamp of keeping discharge lamp;

Drive division does not make the action beginning in the dwell time of regulation after the output from the electric power of controlling power supply unit begins.

2. discharge lamp ignition device as claimed in claim 1 is characterized in that,

Possess the dim signal input part, this dim signal input part is imported dim signal from the outside, and this dim signal is the signal of telecommunication that the light output of discharge lamp is indicated;

Control part is made as and is input to the corresponding frequency of dim signal in the dim signal input part with the frequency of the action of drive division at least in operating stably.

3. discharge lamp ignition device as claimed in claim 1 or 2 is characterized in that possessing:

Unusual judging part is judged to have or not unusual that discharge lamp is turned off the light; And

Clock portion generates clock signal;

Consume when the frequency of the clock signal that control part is exported in clock portion is high more that electric power increases and responsiveness improves, this control part controlling and driving portion is so that be that the output power that reduces at least when unusual to discharge lamp is arranged by unusual judgement section judges;

Clock portion makes the frequency ratio of clock signal low in the action of drive division in the stopping of drive division.

4. discharge lamp ignition device as claimed in claim 3 is characterized in that,

Possess the report power supply unit, the report voltage that this report power supply unit will be stipulated in the action of drive division inputs to clock portion;

Clock portion imported from the report power supply unit report voltage during, the frequency ratio that makes clock signal is not high during the report power supply unit input report voltage.

5. discharge lamp ignition device as claimed in claim 1 is characterized in that,

The power converter that DC power supply portion will be transfused to is a direct current power;

Above-mentioned discharge lamp ignition device possesses the low judging part of input voltage, and whether the low judgement section judges of this input voltage is the low state of input voltage to the input voltage deficiency of DC power supply portion;

By input voltage low judgement section judges be the low state of input voltage during, drive division does not make action beginning.

6. discharge lamp ignition device as claimed in claim 1 is characterized in that,

The power converter that DC power supply portion will be transfused to is a direct current power;

Above-mentioned discharge lamp ignition device possesses:

The low judging part of input voltage judges whether it is the low state of input voltage to the input voltage deficiency of DC power supply portion; And

Non-loaded judging part judges whether it is the no-load condition that does not connect discharge lamp on resonant structure;

By input voltage low judgement section judges be the low state of input voltage during and by non-loaded judgement section judges be no-load condition during, drive division does not make the action beginning.

7. as claim 5 or 6 described discharge lamp ignition devices, it is characterized in that,

Possess storage part, this storage part is made of nonvolatile memory, deposits the ephemeral data that uses in the action of control part;

The deletion that remains on the ephemeral data in the storage part is carried out in the action of drive division.

8. discharge lamp ignition device as claimed in claim 7 is characterized in that,

The action that reads out in drive division of leaving the ephemeral data in the storage part in begins to carry out before.

9. discharge lamp ignition device as claimed in claim 1 or 2 is characterized in that,

Possess the discharge lamp judging part, this discharge lamp judging part judges according to the asymmetrical current that flows whether discharge lamp is end of lifetime in discharge lamp.

10. discharge lamp ignition device as claimed in claim 1 is characterized in that,

Possess rectification part, this rectification part is carried out full-wave rectification to the alternating electromotive force from the outside input;

DC power supply portion comprises following Switching Power Supply, and this Switching Power Supply has the series circuit of switch element between the output of the rectification part of being connected and inductor and is connected in series on the above-mentioned inductor and both end voltage is the output capacitor of the output voltage of DC power supply portion;

Above-mentioned discharge lamp ignition device possesses:

Power drives portion carries out conducting to the switch element of DC power supply portion and disconnects and driving, and remains necessarily with the output voltage with DC power supply portion; And

The unusual judging part of DC power supply detects the output voltage of DC power supply portion, and judges that DC power supply portion is normally or unusual;

If in operating stably, be that DC power supply portion is unusual by the unusual judgement section judges of DC power supply, then control part finishes operating stably and begins once more startup action, in once more startup release but unusual judgement section judges is under the unusual situation of DC power supply portion by DC power supply, drive division is stopped.

11. discharge lamp ignition device as claimed in claim 10 is characterized in that,

Power drives portion arrives the next conducting time before with the switch element of DC power supply portion in case disconnect the back, is made as more than the retention time of regulation.

12., it is characterized in that possessing as claim 10 or 11 described discharge lamp ignition devices:

Timing portion carries out timing to accumulative total service time, and this accumulative total is added up timing service time at least in the action of drive division, and is not reset; And

Overvoltage protection portion, reached service time in accumulative total before time device lifetime of regulation by the timing of timing portion, the output voltage of working as DC power supply portion become assigned voltage when above control power drives portion so that the overvoltage protection action that the output voltage of DC power supply portion descends;

Overvoltage protection portion does not carry out the overvoltage protection action after the accumulative total by the timing of timing portion reaches time device lifetime of regulation service time.

13. discharge lamp ignition device as claimed in claim 1 or 2 is characterized in that,

Possess timing portion, this timing portion carries out timing to accumulative total service time, and this accumulative total is added up timing service time at least in the action of drive division, and is not reset;

Control part is after the accumulative total by the timing of timing portion reaches time device lifetime of regulation service time, and the duration that makes preheating action reaches long before the time device lifetime service time than the accumulative total by the timing of timing portion.

14. discharge lamp ignition device as claimed in claim 1 or 2 is characterized in that,

Possess timing portion, this timing portion carries out timing to accumulative total service time, and this accumulative total is added up timing service time at least in the action of drive division, and is not reset;

Control part makes duration of starting action reach short before the time device lifetime service time than the accumulative total by the timing of timing portion after the accumulative total by the timing of timing portion reaches time device lifetime of regulation service time.

15. discharge lamp ignition device as claimed in claim 1 or 2 is characterized in that,

The driving that possess printed wiring board, is provided with drive division and startup portion at least is with integrated circuit and the control integrated circuit that is provided with control part at least;

In the ground connection figure of earthing potential in the conductive pattern on being located at printed wiring board, that be made as circuit, and drive the position that is electrically connected with circuit with integrated circuit and control, from the position branch that is connected with DC power supply portion, switch portion and resonant structure respectively.

16. a ligthing paraphernalia is characterized in that, the appliance body that possesses claim 1 or 2 described discharge lamp ignition devices and keep discharge lamp ignition device.

17. a supply unit is characterized in that possessing:

DC power supply circuit, have at least 1 inductor and be connected in series in switch element on the inductor, conducting/disconnection by the diverter switch element comes to release energy to inductor savings energy and from inductor repeatedly, thus, will be to being transformed to direct voltage from the direct voltage of DC power supply or from the pulsating voltage that the alternating voltage of AC power has carried out rectification;

Load circuit is accepted the output voltage of DC power supply circuit, and action electric power is supplied with in load;

The output voltage test section, the output voltage of detection DC power supply circuit; And

The DC power supply control circuit, the conducting/disconnection of switching the switch element of DC power supply circuit according to the testing result of output voltage test section is controlled to be the output voltage of DC power supply circuit the voltage of prescribed level thus;

The DC power supply control circuit has:

Zero current detection portion becomes below the predetermined electric current value if flow through the electric current of inductor, then exports zero-signal;

Peak current detection portion becomes more than the predetermined electric current value if flow through the electric current of the switch element of DC power supply circuit, then exports peak signal; And

Drive division switches to conducting corresponding to zero-signal with the switch element of DC power supply circuit, and corresponding to peak signal the switch element of DC power supply circuit is switched to disconnection;

Zero current detection portion possesses shielding part, this shielding part below the electric current that flows through inductor becomes the predetermined electric current value after, among specified time limit, stop drive division output zero-signal.

18. supply unit as claimed in claim 17 is characterized in that,

Above-mentioned DC power supply control circuit has filter section, and this filter section stops among specified time limit drive division output peak signal after the electric current of the switch element that flows through DC power supply circuit becomes more than the predetermined electric current value;

Be set at longer the specified time limit of being set by shielding part than the specified time limit of being set by filter section.

19. supply unit as claimed in claim 17 is characterized in that,

Above-mentioned load is a discharge lamp;

Load circuit possesses:

Converter control circuit has 1 switch element at least, by switching the conducting/disconnection of this switch element, the output voltage of DC power supply circuit is transformed to high frequency voltage;

The low judging part of voltage is located in the DC power supply control circuit, judges whether the output voltage of DC power supply circuit is lower than the low-voltage of the regulation lower than afore mentioned rules voltage; And

Sequential control portion, at least during following two, carry out sequential control, be respectively during above-mentioned two: control change device control circuit with discharge lamp is supplied with between the starting period that starts required electric power and control change device control circuit with discharge lamp is supplied with keep the lighting a lamp of the required electric power of lighting a lamp during;

Sequential control portion is controlled to be: if be to be lower than the low-voltage of regulation then to switch between the starting period by the low judgement section judges of voltage, and through switch to after the stipulated time light a lamp during.

20. as each described supply unit in the claim 17～19, it is characterized in that,

Above-mentioned DC power supply control circuit possesses:

Voltage rising judging part, whether the output voltage of judging DC power supply circuit surpasses the 1st regulation overvoltage higher than afore mentioned rules voltage, if and be judged as and surpassed the 1st regulation overvoltage, then the switch element of DC power supply control circuit is switched to disconnection by drive division; And

Begin portion again, to carrying out timing the opening time of the switch element of DC power supply control circuit, and if the time of timing surpass specified time limit, then the switch element of DC power supply control circuit is switched to conducting by drive division;

Voltage rising judging part is under the situation of off-state at the switch element of DC power supply circuit, whether the output voltage of judging DC power supply circuit is lower than the 2nd regulation overvoltage lower than the 1st regulation overvoltage, the portion that begins again is judged as DC power supply circuit from voltage rising judging part output voltage was lower than for the 2nd superpotential moment of regulation, to carrying out timing the opening time of the switch element of DC power supply control circuit.

21. a supply unit is characterized in that possessing:

DC power supply portion, by power supply supply capability from the outside, and output DC power;

Power converter portion exports with the direct current power proper transformation of DC power supply portion output and to load;

The unusual judging part of mains side judges that DC power supply portion has or not abnormality;

The unusual judging part of load-side judges that at least one side of power converter portion and load has or not abnormality; And

Control part according to the judgement of the unusual judging part of mains side and the judgement of the unusual judging part of load-side, is controlled power converter portion at least;

Control part before the beginning operating stably, makes from power converter portion to the startup action more medium and small than operating stably of the output power of load when starting;

Control part continues to carry out startup action once more at the appointed time when being abnormality by the unusual judgement section judges of mains side;

When being abnormality, only, the output of power converter portion is stopped in that unusual judgement section judges is not under the situation of abnormality by mains side by the unusual judgement section judges of load-side.

22. supply unit as claimed in claim 21 is characterized in that,

Control part if be abnormality by the unusual judgement section judges of mains side still when startup release once more, then makes the output of power converter portion stop after unusual judgement section judges is abnormality by mains side at least.

23. as claim 21 or 22 described supply units, it is characterized in that,

Control part is counted the number of times that once more startup action is performed;

After the number of times that once more startup action is begun reaches the set upper limit number of times, when being abnormality, not beginning startup action once more, and the output of power converter portion is stopped by the unusual judgement section judges of mains side.

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