CN101694963A - High-precision low-voltage voltage/current switching circuit - Google Patents
High-precision low-voltage voltage/current switching circuit Download PDFInfo
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- CN101694963A CN101694963A CN 200910180793 CN200910180793A CN101694963A CN 101694963 A CN101694963 A CN 101694963A CN 200910180793 CN200910180793 CN 200910180793 CN 200910180793 A CN200910180793 A CN 200910180793A CN 101694963 A CN101694963 A CN 101694963A
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Abstract
The invention relates to a high-precision low-voltage voltage/current switching circuit. The circuit comprises a current mirror, a voltage following circuit, an error amplifier and a first resistor, wherein the current mirror comprises a first transistor and a third transistor, the first end of the first transistor and the first end of the third transistor are connected with input voltage, and the second end of the first transistor and the second end of the third transistor are respectively connected with the voltage following circuit; the voltage following circuit is used for enabling the voltages of the second end of the first transistor and the second end of the third transistor, which are connected with the voltage following circuit, to be equal; the first input end of the error amplifier receives reference voltage, and the second input end of the error amplifier is connected to the voltage following circuit; and the first resistor is connected with the second input end of the error amplifier so as to obtain first current and then copies the first current to obtain output current. In the invention, the voltage/current switching circuit has low working voltage, strong power source change inhibiting ability as well as simple and reliable circuit structure so that the invention is widely applied to analog integrated circuits.
Description
Technical field
The present invention relates to analog integrated circuit, relate in particular to voltage-current converter circuit.
Background technology
In integrated circuit (IC) system, the mutual conversion between the electric current and voltage is very general.As in Digital Analog Hybrid Circuits or in electric power management circuit; accurate reference voltage can provide an accurate reference over the ground for whole system; the overvoltage protection of system, overcurrent protection, overtemperature protection, error amplifier, comparator all need a reference point accurately; but in being full of the system of noise; if from the direct transfer overvoltage signal of a reference source to needed module; the interference of parasitic parameters such as placement-and-routing will be easy to be subjected to; slight interference can cause the decline of systematic function, and serious disturbance causes systemic-function unusual possibly.Therefore by converting reference voltage to electric current, carry out signal transmission between the module by electric current, then will strengthen greatly,, reach the accurate transmission of reference voltage the most at last if again electric current is reduced into reference voltage in local module for the inhibition ability of parasitic disturbances.
Fig. 1 is a kind of voltage-current converter circuit of the prior art.This voltage-current converter circuit has adopted the CASCODE current-mirror structure, but minimum operating voltage is higher, is about 3.05 volts.
Fig. 2 is an another kind of voltage-current converter circuit of the prior art.This voltage-current converter circuit adopts CASCODE structure current mirror, and minimum operating voltage is about 2.45 volts; And increased resistance R 3, and then increased integrated circuit chip area, simultaneously, R3 is subjected to effect of process variations easily, R3 can change with flow-route and temperature the bias voltage that M4, M5, M6 form, very likely make M4, M5, M6 enter linear zone, weaken the effect of the accurate replica current of CASCDOE current mirror greatly.
Fig. 3 is another voltage-current converter circuit of the prior art.This voltage-current converter circuit current mirror precision is low, and output voltage can not accurately reduce.
Summary of the invention
The invention provides a kind of voltage-current converter circuit of the high accuracy low-voltage that can overcome the above problems.
In first aspect, the invention provides a kind of voltage-current converter circuit, comprise reference voltage, input voltage, output current, and comprise current mirror, voltage follower circuit, error amplifier and first resistance.
This current mirror comprises the first transistor and the 3rd transistor, and this first transistor first end, the 3rd transistor first end link to each other with input voltage, and this first transistor the 3rd end, the 3rd transistor the 3rd end link to each other with this error amplifier output.This voltage follower circuit comprises first branch road and the 3rd branch road, this first branch road, first end links to each other with this first transistor second end, the 3rd branch road first end links to each other with the 3rd transistor second end, and this voltage follower circuit is used to make coupled the 3rd transistor second terminal voltage to equal this first transistor second terminal voltage.
This error amplifier first input end receives reference voltage, and second input is connected to this voltage follower circuit first branch road, so that this error amplifier, this voltage follower circuit, this first transistor constitute negative feedback loop.This first resistance links to each other with this voltage follower circuit first branch road obtaining first electric current, thereby obtains output current by duplicating this first electric current again.
In one embodiment of the invention, second branch road that comprises output voltage terminal, transistor seconds and second resistance and voltage follower circuit.This transistor seconds first end links to each other with input voltage, and this transistor seconds second end links to each other with voltage follower circuit second branch road first end, and this transistor seconds the 3rd end links to each other with the error amplifier output.And this voltage follower circuit second branch road second end links to each other with second resistance, and with this tie point as output voltage terminal.
In another embodiment of the present invention, the first transistor, transistor seconds, the 3rd transistor are the PMOS transistor, and the error amplifier first input end is the backward end of this error amplifier.
In yet another embodiment of the present invention, the first transistor, transistor seconds, the 3rd transistor are nmos pass transistor, and the error amplifier first input end is the end in the same way of this error amplifier.
Voltage-current converter circuit operating voltage of the present invention is low, and it is strong that power source change is suppressed ability, and the output current matching is good, and the output voltage reduction is accurate and circuit structure is simple and reliable.
Description of drawings
Below with reference to accompanying drawings specific embodiments of the present invention is described in detail, in the accompanying drawings:
Fig. 1 is a kind of voltage-current converter circuit of the prior art;
Fig. 2 is an another kind of voltage-current converter circuit of the prior art;
Fig. 3 is another voltage-current converter circuit of the prior art;
Fig. 4 is a pmos type voltage-current converter circuit schematic diagram;
Fig. 5 is the pmos type voltage-current converter circuit of Fig. 4 first embodiment;
Fig. 6 is the pmos type voltage-current converter circuit of Fig. 4 second embodiment;
Fig. 7 is the pmos type voltage-current converter circuit of Fig. 4 the 3rd embodiment;
Fig. 8 is the pmos type voltage-current converter circuit of Fig. 4 the 4th embodiment;
Fig. 9 is a nmos type voltage-current converter circuit schematic diagram;
Figure 10 is the nmos type voltage-current converter circuit of Fig. 9 first embodiment;
Figure 11 is the nmos type voltage-current converter circuit of Fig. 9 second embodiment;
Figure 12 is the nmos type voltage-current converter circuit of Fig. 9 the 3rd embodiment;
Figure 13 is the nmos type voltage-current converter circuit of Fig. 9 the 4th embodiment.
Embodiment
Fig. 4 is a pmos type voltage-current converter circuit schematic diagram.Among Fig. 4, PMOS pipe M1, M2, M3 constitute current mirror, and link to each other with input voltage VIN.Reference voltage source produces reference voltage V REF, and this reference voltage V REF is input to the end of oppisite phase of error amplifier EA as input signal, and error amplifier EA output drives this current mirror makes it produce image current and output respectively.Voltage follower circuit comprises first branch road, second branch road and the 3rd branch road, and this first branch road, first end (A point) links to each other with the M1 drain electrode, and this second branch road, first end (B point) links to each other with the M2 drain electrode, and the 3rd branch road first end (C point) links to each other with the M3 drain electrode; And this voltage follower circuit is used to make coupled M2 drain voltage, M3 drain voltage to follow the M1 drain voltage, B point, C point are equated with the A point voltage, be VA=VB=VC, so that M1, M2, M3 source gate drain voltage equate respectively and then realize the accurate mirror image of electric current.Resistance R 1 links to each other to obtain electric current I 1 with voltage follower circuit first branch road.
Fig. 5 is the pmos type voltage-current converter circuit of Fig. 4 first embodiment.Among Fig. 5, voltage follower circuit comprises metal-oxide-semiconductor M4, M5, M6, and M1 drain electrode links to each other with the M4 source electrode, and the M2 drain electrode links to each other with the M5 source electrode, and M3 drains and links to each other with the M6 source electrode, so that this M1, M2, M3, M4, M5, M6 formation CASCODE structure current mirror.The diode syndeton that M4 adopts grid drain electrode to link to each other is so that M4 provides bias voltage for M5, M6.M4, M5, M6 grid link to each other, and then electric current I 2 replication streams of the M2 that flows through, M5 are through M1, M4 electric current I 1, and electric current I 3 replication streams of the M3 that flows through, M6 are through M2, M5 electric current I 2, thereby obtain output current I3.In one embodiment of the invention, M4 is adopted the diode syndeton replace to and add fixed bias voltage in M4, M5, the employing of M6 grid.
Among Fig. 5, error amplifier EA in-phase end VN links to each other with metal-oxide-semiconductor M4 drain electrode, forms a negative feedback loop.This negative feedback loop comprises metal-oxide-semiconductor M1, M4 and error amplifier EA, and this error amplifier EA in-phase end VN is the end of oppisite phase of this negative feedback loop.The effect of this negative feedback loop is in order to guarantee that the VN terminal voltage equals reference voltage V REF.Resistance R 1 links to each other with error amplifier EA in-phase end VN, and the R1 electric current I 1 of therefore flowing through equals VN voltage divided by resistance R 1, i.e. the electric current I 1 that I1=VREF/R1, so VN produces on resistance R 1 is equivalent to the electric current that reference voltage V REF produces on R1.Resistance R 2 one ends and M5 drain electrode link to each other and with this tie point as output voltage V 0 end, resistance R 2 other ends link to each other with resistance R 1, and V0=I2*R2, wherein electric current I 2 obtains by duplicating the I1 electric current.
Design M1, M2, M3 mate mutually, be that M1, M2, M3 are that same type metal-oxide-semiconductor and its breadth length ratio are proportional, then the ratio of electric current I 1, I2, I3 equals the ratio of M1, M2, M3 breadth length ratio, and owing to I1=VREF/R1, therefore can proportionally duplicate by I1 and obtain I2, I3.In a preferred embodiment of the invention, M4, M5, M6 mate mutually, to form precise current mirror coupling.Because I2=V0/R2, I1=VREF/R1, V0=a* (R2/R1) VREF then, wherein coefficient a is M2 and the ratio of M1 breadth length ratio, so output voltage V 0 can by reference voltage V REF proportionally a* (R2/R1) duplicate and obtain.The then Vgs4=Vds4 because the M4 grid drain electrode links to each other, and then the minimum voltage that M4 is operated in the saturation region is Vgs4, so the minimum voltage VIN (min) of voltage-current converter circuit work is:
VIN(min)＝Vds_sat1+Vgs4+VREF (1)
Wherein, Vds_sat1 is the minimum saturation voltage of M1.Vds_sat1 is about 0.2 volt, and Vgs4 is about 0.8 volt, and VREF is 1.25V, and then minimum voltage VIN (min) equals 2.25 volts.2.25 volt voltage has been near or below the supply voltage threshold value of common reference voltage source work, so Fig. 5 circuit is a high-precision voltage-current converter circuit of low-voltage.
Fig. 6 is the pmos type voltage-current converter circuit of Fig. 4 second embodiment, and Fig. 6 circuit is a preferable embodiment of Fig. 4 circuit.Among Fig. 6, voltage follower circuit comprises metal-oxide-semiconductor M4, M5, M6 and resistance R 3; This M1 drain electrode links to each other with the M4 source electrode, and the M2 drain electrode links to each other with the M5 source electrode, and the M3 drain electrode links to each other with the M6 source electrode; M4, M5, M6 grid link to each other, and then electric current I 2 replication streams of the M2 that flows through, M5 are through M1, M4 electric current I 1, and electric current I 3 replication streams of the M3 that flows through, M6 are through M2, M5 electric current I 2, thereby obtain output current I3.
Among Fig. 6, error amplifier EA in-phase end VN links to each other with metal-oxide-semiconductor M4 drain electrode, forms a negative feedback loop.This negative feedback loop comprises metal-oxide-semiconductor M1, M4 and error amplifier EA.Resistance R 3 one ends link to each other with this error amplifier EA in-phase end VN, the other end links to each other with M4 grid and resistance R 1, and this tie point is designated as the D point, and resistance R 1 electric current I 1 of therefore flowing through equals VREF/ (R1+R3), D point voltage VD equals I1*R3, i.e. VD=VREF*R1/ (R1+R3).Resistance R 2 one ends and M5 drain electrode link to each other and with this tie point as output voltage V 0 end, resistance R 2 other ends link to each other with resistance R 1, then output voltage V 0 equals I2*R2, wherein electric current I 2 obtains by duplicating the I1 electric current.
Design M1, M2, M3 mate mutually, and then the ratio of electric current I 1, I2, I3 equals the ratio of M1, M2, M3 breadth length ratio.And because I1=VREF/ (R1+R3) therefore can proportionally duplicate by I1 and obtain I2, I3.In a preferred embodiment of the invention, M4, M5, M6 mate mutually, because I2=V0/R2, I1=VREF/ (R1+R3), then output voltage V 0 equals a*VREF*R2/ (R1+R3), wherein coefficient a is M2 and the ratio of M1 breadth length ratio, thus output voltage V 0 can by reference voltage V REF proportionally a*R2/ (R1+R3) duplicate and obtain.The minimum voltage that M4 is operated in the saturation region is Vgs4, so the minimum voltage VIN (min) of voltage-current converter circuit work is:
VIN(min)＝Vds_sat1+Vgs4+VD＝Vds_sat1+Vgs4+VREF*R1/(R1+R3)(2)
Wherein, Vds_sat1 is the minimum saturation voltage of M1.Vds_sat1 is about 0.2 volt, and Vgs4 is about 0.8 volt, and VREF is 1.25V, VD=0.2V, and then minimum voltage VIN (min) equals 1.2 volts.1.2 volt voltage is lower than the supply voltage threshold value of common reference voltage source work; And with respect to Fig. 5, the minimum power supply voltage, VIN (min) among Fig. 6 reduces greatly with input reference voltage VREF correlation, and promptly minimum power supply voltage, VIN (min) is subjected to input reference voltage VREF to influence less.
Fig. 7 is the pmos type voltage-current converter circuit of Fig. 4 the 3rd embodiment.Among Fig. 7, voltage follower circuit comprises metal-oxide-semiconductor M4, M5, M6, M7, M8, M9 and resistance R 3, and M1, M4, M7 and M2, M5, M8 and M3, M6, M9 form CASCODE structure current mirror, and the M4 grid links to each other with the M7 drain electrode.R3 one end is held in the same way with error amplifier EA and is linked to each other, and the other end links to each other with resistance R 1 and M7 grid.
Fig. 8 is the pmos type voltage-current converter circuit of Fig. 4 the 4th embodiment.Among Fig. 8, voltage follower circuit comprises metal-oxide-semiconductor M4, M5, M6, M7, M8, M9 and resistance R 3, R4, and M1, M4, M7 and M2, M5, M8 and M3, M6, M9 form CASCODE structure current mirror.R4 one end is held in the same way with error amplifier EA and is linked to each other, and the other end links to each other with the M4 grid and this tie point is designated as the D point.R3 one end is connected to the D point, and the other end links to each other with resistance R 1.
The voltage-current converter circuit of high accuracy low-voltage of the present invention is not limited to Fig. 4, Fig. 5, Fig. 6, Fig. 7, Fig. 8 circuit diagram, and transistor also can adopt other as transistors such as NMOS, BJT in the circuit of the present invention.Be that the NMOS pipe is that example is set forth with M1, M2, M3 below, Fig. 9 is a nmos type voltage-current converter circuit schematic diagram.
Among Fig. 9, NMOS pipe M1, M2, M3 constitute current mirror, and link to each other with input voltage VIN respectively.Reference voltage source produces reference voltage V REF, and this reference voltage V REF is input to the in-phase end of error amplifier EA as input signal, and error amplifier EA output drives this current mirror makes it produce image current and output respectively.Voltage follower circuit comprises first branch road, second branch road and the 3rd branch road, and this first branch road, first end (A point) links to each other with the M1 source electrode, and this second branch road, first end (B point) links to each other with the M2 source electrode, and the 3rd branch road first end (C point) links to each other with the M3 source electrode; And this voltage follower circuit is used to make coupled M2 source voltage, M3 source voltage to follow the M1 source voltage, B point, C point are equated with the A point voltage, be VA=VB=VC, so that M1, M2, M3 source gate drain voltage equate respectively and then realize the accurate mirror image of electric current.Resistance R 1 links to each other to obtain electric current I 1 with voltage follower circuit first branch road.
Figure 10 is the nmos type voltage-current converter circuit of Fig. 9 first embodiment.Voltage follower circuit in this voltage-current converter circuit comprises metal-oxide-semiconductor M4, M5, M6, and the M1 source electrode links to each other with the M4 source electrode, the M2 source electrode links to each other with the M5 source electrode, and the M3 source electrode links to each other with the M6 source electrode, so that this M1, M2, M3, M4, M5, M6 constitute CASCODE structure current mirror.Error amplifier EA end of oppisite phase VN links to each other with the M4 drain electrode, forms a negative feedback loop.Resistance R 1 links to each other with error amplifier EA end of oppisite phase VN, and the R1 electric current I 1 of therefore flowing through equals VN voltage divided by resistance R 1.Resistance R 2 one ends and M5 drain electrode link to each other and with this tie point as output voltage V 0 end, the other end links to each other with resistance R 1, V0=I2*R2 then, wherein electric current I 2 obtains by duplicating the I1 electric current.
Design M1, M2, M3 mate mutually, and then the ratio of electric current I 1, I2, I3 equals the ratio of M1, M2, M3 breadth length ratio.In a preferred embodiment of the invention, M4, M5, M6 mate mutually, and the minimum voltage VIN (min) of this voltage-current converter circuit work equals Vds_sat+Vgs1+Vgs4+VREF.Wherein, Vds_sat is the maximum amplitude of oscillation restriction of output voltage error amplifier, and Vds_sat is about 0.2 volt, M1 gate source voltage Vgs1 is 1 volt (consideration bulk effect), M4 gate source voltage Vgs4 is about 0.8 volt, and VREF is 1.25V, and then minimum voltage VIN (min) equals 3.25 volts.3.25 volt voltage has been near or below the supply voltage threshold value of common reference voltage source work, so Figure 10 circuit is the voltage-current converter circuit of a high accuracy low-voltage.
Figure 11 is the nmos type voltage-current converter circuit of Fig. 9 second embodiment.This Figure 11 is the preferable embodiment of Fig. 9.Among Figure 11, voltage follower circuit comprises metal-oxide-semiconductor M4, M5, M6 and resistance R 3; This M1 source electrode links to each other with the M4 source electrode, and the M2 source electrode links to each other with the M5 source electrode, and the M3 source electrode links to each other with the M6 source electrode, so that this M1, M2, M3, M4, M5, M6 constitute CASCODE structure current mirror.Error amplifier EA end of oppisite phase VN links to each other with metal-oxide-semiconductor M4 drain electrode, forms a negative feedback loop, and this negative feedback loop comprises metal-oxide-semiconductor M1, M4 and error amplifier EA, and this error amplifier EA end of oppisite phase VN is the end of oppisite phase of this negative feedback loop.Resistance R 3 one ends link to each other with error amplifier EA end of oppisite phase VN, and the other end links to each other with M4 grid and resistance R 1, and this tie point is designated as the D point, and resistance R 1 electric current I 1 of therefore flowing through equals VREF/ (R1+R3), and D point voltage VD equals VD=VREF*R1/ (R1+R3).Resistance R 2 one ends and M5 drain electrode link to each other and with this tie point as output voltage V 0 end, resistance R 2 other ends link to each other with resistance R 1, output voltage V 0=I2*R2=a*VREF*R2/ (R1+R3) then, wherein electric current I 2 obtains by duplicating the I1 electric current, and coefficient a is the ratio of M2, M1 breadth length ratio.
Design M1, M2, M3 mate mutually, and then the ratio of electric current I 1, I2, I3 equals the ratio of M1, M2, M3 breadth length ratio, and in a preferred embodiment of the invention, M4, M5, M6 mate mutually, and then have formed precise current mirror coupling.And minimum power supply voltage, VIN (min) satisfies,
VIN(min)＝Vds_sat+Vgs1+Vgs4+VD (3)
Wherein, Vds_sat is the maximum amplitude of oscillation restriction of output voltage error amplifier, and Vds_sat equals 0.2 volt, and Vgs1 equals 1 volt (consideration bulk effect), and Vgs4 equals 0.8 volt, and VD equals 0.2 volt, and then minimum power supply voltage, VIN (min) equals 2.2 volts.2.2 volt has been near or below the supply voltage threshold value of common reference voltage source work, and well below the conventional voltage current converter circuit structure of NMOS pipe for the adjustment pipe; And with respect to Figure 10, the minimum power supply voltage, VIN (min) among Figure 11 and input reference voltage VREF correlation reduce greatly, and promptly influenced by VREF less for VIN (min).
Figure 12 is the nmos type voltage-current converter circuit of Fig. 9 the 3rd embodiment.Among Figure 12, voltage follower circuit comprises metal-oxide-semiconductor M4, M5, M6, M7, M8, M9 and resistance R 3, and M1, M4, M7 and M2, M5, M8 and M3, M6, M9 form CASCODE structure current mirror, and the M4 grid links to each other with the M7 drain electrode.R3 one end links to each other with error amplifier EA backward end, and the other end links to each other with resistance R 1 and M7 grid.
Figure 13 is the nmos type voltage-current converter circuit of Fig. 9 the 4th embodiment.Among Figure 13, voltage follower circuit comprises metal-oxide-semiconductor M4, M5, M6, M7, M8, M9 and resistance R 3, R4, and M1, M4, M7 and M2, M5, M8 and M3, M6, M9 form CASCODE structure current mirror.R4 one end links to each other with error amplifier EA backward end, and the other end links to each other with the M4 grid and this tie point is designated as the D point.R3 one end is connected to the D point, and the other end links to each other with resistance R 1.
Need to prove, the present invention can be by increasing one or more groups CASCODE structure to improve the current replication precision, but minimum input voltage VIN this moment (min) can improve a lot, and therefore not requiring under the low situation of input voltage, can increase the CASCODE structure.
Obviously, under the prerequisite that does not depart from true spirit of the present invention and scope, the present invention described here can have many variations.Therefore, the change that all it will be apparent to those skilled in the art that all should be included within the scope that these claims contain.The present invention's scope required for protection is only limited by described claims.
Claims (14)
1. a voltage-current converter circuit comprises reference voltage (VREF), input voltage (VIN), output current (I3), it is characterized in that, comprises current mirror, voltage follower circuit, error amplifier (EA) and first resistance (R1);
This current mirror comprises the first transistor (M1) and the 3rd transistor (M3), this the first transistor (M1) first end, the 3rd transistor (M3) first end link to each other with described input voltage (VIN), and this first transistor (M1) the 3rd end, the 3rd transistor (M3) the 3rd end link to each other with described error amplifier (EA) output;
This voltage follower circuit comprises first branch road and the 3rd branch road, this first branch road, first end (A) links to each other with this first transistor (M1) second end, the 3rd branch road first end (C) links to each other with the 3rd transistor (M3) second end, and this voltage follower circuit is used to make coupled the 3rd transistor (M3) second terminal voltage to equal the first transistor (M1) second terminal voltage;
This error amplifier (EA) first input end receives described reference voltage (VREF), second input is connected to this voltage follower circuit first branch road, so that this error amplifier (EA), this voltage follower circuit, this first transistor (M1) constitute negative feedback loop;
Described first resistance (R1) links to each other with this voltage follower circuit first branch road to obtain first electric current (I1), again by duplicating this first electric current (I1) thus obtain output current (I3).
2. a kind of voltage-current converter circuit as claimed in claim 1 is characterized in that, comprises second branch road of output voltage (V0) end, transistor seconds (M2), second resistance (R2) and described voltage follower circuit;
This transistor seconds (M2) first end links to each other with described input voltage (VIN), this transistor seconds (M2) second end links to each other with described voltage follower circuit second branch road, first end (B), and this transistor seconds (M2) the 3rd end links to each other with described error amplifier (EA) output;
This voltage follower circuit second branch road second end links to each other with described second resistance (R2), and this tie point is held as described output voltage (V0).
3. a kind of voltage-current converter circuit as claimed in claim 2 is characterized in that, described voltage follower circuit first branch road comprises the 4th transistor (M4), and the 4th transistor (M4) first end is this first branch road, first end; Described second branch road comprises the 5th transistor (M5), and the 5th transistor (M5) first end is this second branch road, first end; Described the 3rd branch road comprises the 6th transistor (M6), and the 6th transistor (M6) first end is the 3rd branch road first end;
And the 4th transistor (M4) the 3rd end, the 5th transistor (M5) the 3rd end, the 6th transistor (M6) the 3rd end link to each other.
4. a kind of voltage-current converter circuit as claimed in claim 3 is characterized in that, described the 4th transistor (M4) adopts the diode syndeton.
5. a kind of voltage-current converter circuit as claimed in claim 3 is characterized in that, described the 4th transistor (M4), the 5th transistor (M5), the 6th transistor (M6) adopt and add fixed bias voltage.
6. a kind of voltage-current converter circuit as claimed in claim 2, it is characterized in that, described voltage follower circuit first branch road comprises the 4th transistor (M4) and the 3rd resistance (R3), the 3rd resistance (R3) end links to each other with the 4th transistor (M4) the 3rd end, the other end link to each other with the 4th transistor (M4) second end and with this tie point as the tie point that links to each other with described error amplifier (EA);
Described voltage follower circuit second branch road comprises the 5th transistor (M5), this voltage follower circuit the 3rd branch road comprises the 6th transistor (M6), and the 4th transistor (M4) the 3rd end, the 5th transistor (M5) the 3rd end, the 6th transistor (M6) the 3rd end link to each other.
7. a kind of voltage-current converter circuit as claimed in claim 2, it is characterized in that, described voltage follower circuit first branch road comprises the 4th transistor (M4), the 7th transistor (M7) and the 3rd resistance (R3), second branch road comprises the 5th transistor (M5), the 8th transistor (M8), and the 3rd branch road comprises the 6th transistor (M6), the 9th transistor (M9);
This first transistor (M1), the 4th transistor (M4), the 7th transistor (M7) constitute first group of CASCODE structure current mirror, and the 4th transistor (M4) the 3rd end links to each other with the 7th transistor (M7) second end and the 3rd resistance (R3), and with this tie point as the tie point that links to each other with described error amplifier;
This transistor seconds (M2), the 5th transistor (M5) and the 8th transistor (M8) constitute second group of CASCODE structure current mirror; The 6th transistor (M6), the 9th transistor (M9) constitute the 3rd group of CASCODE structure current mirror.
8. a kind of voltage-current converter circuit as claimed in claim 2, it is characterized in that, described voltage follower circuit first branch road comprises the 4th transistor (M4), the 7th transistor (M7), the 3rd resistance (R3) and the 4th resistance (R4), second branch road comprises the 5th transistor (M5), the 8th transistor (M8), and the 3rd branch road comprises the 6th transistor (M6), the 9th transistor (M9);
This first transistor (M1), the 4th transistor (M4), the 7th transistor (M7) constitute first group of CASCODE structure current mirror, and the 4th transistor (M4) the 3rd end links to each other with the 4th resistance (R4) second end, the 3rd resistance (R3) first end, the 3rd resistance (R3) second end links to each other with the 7th transistor (M7) the 3rd end, and the 7th transistor (M7) second end links to each other with the 4th resistance (R4) first end, and with this tie point as the tie point that links to each other with described error amplifier;
This transistor seconds (M2), the 5th transistor (M5) and the 8th transistor (M8) constitute second group of CASCODE structure current mirror; The 6th transistor (M6), the 9th transistor (M9) constitute the 3rd group of CASCODE structure current mirror.
9. a kind of voltage-current converter circuit as claimed in claim 2 is characterized in that, described the first transistor (M1), transistor seconds (M2), the 3rd transistor (M3) be coupling mutually.
10. as claim 3 or 6 or 7 or 8 described a kind of voltage-current converter circuits, it is characterized in that described the 4th transistor (M4), the 5th transistor (M5), the 6th transistor (M6) be coupling mutually.
11. a kind of voltage-current converter circuit as claimed in claim 2, it is characterized in that, described the first transistor (M1), transistor seconds (M2), the 3rd transistor (M3) are the PMOS transistor, and this error amplifier (EA) first input end is the backward end of this error amplifier (EA).
12. a kind of voltage-current converter circuit as claimed in claim 2, it is characterized in that, described the first transistor (M1), transistor seconds (M2), the 3rd transistor (M3) are nmos pass transistor, and this error amplifier (EA) first input end is the end in the same way of this error amplifier (EA).
13. a kind of voltage-current converter circuit as claimed in claim 1 is characterized in that, described reference voltage (VREF) is provided by reference voltage source.
14. a kind of voltage-current converter circuit as claimed in claim 1 is characterized in that, comprises many group CASCODE structures.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 200910180793 CN101694963B (en) | 2009-09-22 | 2009-10-22 | High-precision low-voltage voltage/current switching circuit |
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| CN 200910180793 CN101694963B (en) | 2009-09-22 | 2009-10-22 | High-precision low-voltage voltage/current switching circuit |
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| CN101694963A true CN101694963A (en) | 2010-04-14 |
| CN101694963B CN101694963B (en) | 2013-09-18 |
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| CN102323551A (en) * | 2011-09-14 | 2012-01-18 | 开源集成电路(苏州)有限公司 | Circuit for detecting locked point current of micro motor |
| CN102541139A (en) * | 2012-01-19 | 2012-07-04 | 浙江中控技术股份有限公司 | System and method for outputting of analog quantity current |
| CN102938557A (en) * | 2012-11-23 | 2013-02-20 | 聚辰半导体(上海)有限公司 | Novel enable control circuit for power management system |
| CN107425845A (en) * | 2017-05-08 | 2017-12-01 | 华为技术有限公司 | A kind of superposition circuit and floating voltage D/A converting circuit |
| CN109765958A (en) * | 2019-03-29 | 2019-05-17 | 西安中颖电子有限公司 | A kind of constant current source driving circuit based on bicyclic negative-feedback |
| CN111386509A (en) * | 2017-12-28 | 2020-07-07 | 德州仪器公司 | Voltage protection circuit |
| CN114415773A (en) * | 2022-01-20 | 2022-04-29 | 广州昂瑞微电子技术有限公司 | High-precision current source circuit |
Family Cites Families (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5793248A (en) * | 1996-07-31 | 1998-08-11 | Exel Microelectronics, Inc. | Voltage controlled variable current reference |
| CN100543632C (en) * | 2003-08-15 | 2009-09-23 | Idt-紐威技术有限公司 | Adopt the precise voltage/current reference circuit of current-mode technology in the CMOS technology |
| CN1259610C (en) * | 2004-07-08 | 2006-06-14 | 清华大学 | Virtual earth circuit in current detector of microcomputer multiphase switch power source |
| JP2008016732A (en) * | 2006-07-07 | 2008-01-24 | Mitsumi Electric Co Ltd | Light-emitting diode driving circuit |
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| CN102323551A (en) * | 2011-09-14 | 2012-01-18 | 开源集成电路(苏州)有限公司 | Circuit for detecting locked point current of micro motor |
| CN102541139A (en) * | 2012-01-19 | 2012-07-04 | 浙江中控技术股份有限公司 | System and method for outputting of analog quantity current |
| CN102541139B (en) * | 2012-01-19 | 2013-12-18 | 浙江中控技术股份有限公司 | System and method for outputting of analog quantity current |
| CN102938557A (en) * | 2012-11-23 | 2013-02-20 | 聚辰半导体(上海)有限公司 | Novel enable control circuit for power management system |
| CN107425845A (en) * | 2017-05-08 | 2017-12-01 | 华为技术有限公司 | A kind of superposition circuit and floating voltage D/A converting circuit |
| US10804923B2 (en) | 2017-05-08 | 2020-10-13 | Huawei Technologies Co., Ltd | Superposition operation circuit and float-voltage digital-to-analog conversion circuit |
| CN111386509A (en) * | 2017-12-28 | 2020-07-07 | 德州仪器公司 | Voltage protection circuit |
| CN111386509B (en) * | 2017-12-28 | 2022-07-26 | 德州仪器公司 | Voltage protection circuit, transceiver and voltage protection method |
| CN109765958A (en) * | 2019-03-29 | 2019-05-17 | 西安中颖电子有限公司 | A kind of constant current source driving circuit based on bicyclic negative-feedback |
| CN114415773A (en) * | 2022-01-20 | 2022-04-29 | 广州昂瑞微电子技术有限公司 | High-precision current source circuit |
| CN114415773B (en) * | 2022-01-20 | 2024-03-19 | 广州昂瑞微电子技术有限公司 | High-precision current source circuit |
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