CN101320060A - Fast phase meter - Google Patents
Fast phase meter Download PDFInfo
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- CN101320060A CN101320060A CNA2008101168536A CN200810116853A CN101320060A CN 101320060 A CN101320060 A CN 101320060A CN A2008101168536 A CNA2008101168536 A CN A2008101168536A CN 200810116853 A CN200810116853 A CN 200810116853A CN 101320060 A CN101320060 A CN 101320060A
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Abstract
The invention provides a quick phase meter relates to the measuring field of signal and phase. After a measured signal 1 and a measured signal 2 enter into corresponding signal modulating circuits, the amplitudes of the measured signal 1 and the measured signal 2 are firstly modulated; under the uniform sampling control, high-speed A/D sampling samples the measured signal 1 and the measured signal 2 to form a digital signal 1 and a digital signal 2. After being buffered by corresponding data, the digital signal 1 and the digital signal 2 are respectively processed in the way of data redundancy pretreatment, FFT conversion, spectral peak searching, arc tangent circulation and so on, thereby obtaining the accurate instantaneous phase data of the measured signal 1 and the measured signal 2 and working out the phase difference between the two measured signals. The quick phase meter can provide phase difference between the two measured signals through the data redundancy pretreatment and also can work out the respective instantaneous phase value of the measured signals at the same time, thereby overcoming the defect of the prior phase meter which can not provide the instantaneous phase values of measured signals.
Description
Technical field
The present invention relates to the signal phase fields of measurement, is the fast phase meter that a kind of phase differential that has between accurate measurement measured signal can provide each measured signal accurate instantaneous phase value function simultaneously.
Background technology
Phase measurement is widely used in every field such as national defence, scientific research, production, electric power, mechanical engineering application, and the requirement of phase measurement is also progressively developed to high precision, high-intelligentization direction.Phase measurement scheme has multiple: pulse pad count method, and measured signal is made into square-wave signal and forms the pulse width signal of output pulse sequence, obtain the phase differential between the counting number reflection measured signal of high-frequency impulse with this control gate circuit; The phase demodulation method, measured signal is shaped to square-wave signal and makes phase discrimination processing through NOR gate circuit, obtains the amplitude of the DC component that is directly proportional with phase differential again through smothing filtering; Also comprise voltage table method etc. in addition.These methods have its accommodation separately, and circuit has nothing in common with each other, and need special-purpose device, and the hardware cost height brings very big inconvenience to use.Existing in addition phase measurement scheme can't provide the accurate instantaneous phase value of each measured signal.Along with the development of Digital Electronic Technique and microcomputer technology, phase measurement also develops to the digitizing direction gradually in recent years.The digitizing phase measurement scheme has that hardware cost is low, dirigibility is strong, and the precision height can be adapted to different measuring objects by changing core algorithm.
The present invention gets the phase differential that difference can obtain measured signal then by measuring the accurate instantaneous phase place of each measured signal, and can utilize classical fft algorithm to finish phase measurement.Because classical fft algorithm causes the phase information of the measured signal of calculating inaccurate because of sample frequency and measured signal frequency have deviation when calculating the measured signal spectrum information, can't directly use.Among the present invention, measured signal is calculated through data redundancy pre-service carrying out then FFT earlier behind over-sampling, at this moment can obtain the instantaneous phase value of measured signal, thereby finally obtain phase differential.All calculating of the present invention are all finished at numeric field, and utilize classical fft algorithm, calculate simply fast, and the digital processing chip of high speed easy to use is finished, and helps reducing hardware complexity, saves cost.
Summary of the invention
The present invention is the deficiency that overcomes existing equipment, a kind of fast phase meter is provided, measured signal 1 and measured signal 2 are after sampling, by means of the data redundancy treatment technology, the digital sequence of 2N-1 point separately is compressed into the corresponding digital sequence of N point then through the FFT transformation calculations, spectrum peak search and arctangent computation obtain the accurate instantaneous phase value of corresponding measured signal 1 and measured signal 2, the difference of the instantaneous phase value of gained measured signal 1 and measured signal 2 promptly is the phase differential between measured signal, and the accurate instantaneous phase value and the phase differential thereof of gained measured signal 1 and measured signal 2 show after display process.The scope of application of measured signal of the present invention is wider, and its upper limit depends on the performance of high-speed a/d sampling A, has the test duration consistance in whole tested scope, has overcome existing method and has measured long shortcoming of low-frequency phase potential difference time.By means of the FFT technology, be beneficial to and use digital signal processing chip to realize phase difference measurement, simplified hardware complexity, reduced system cost.
For achieving the above object, provide a kind of fast phase meter, comprised following processing procedure:
Step 1, measured signal 1 and measured signal 2 are input to the corresponding signal modulate circuit, and amplitude obtains conditioning, and little measured signal obtains amplifying, and big measured signal obtains decay, and the amplitude of signal is controlled near the full amplitude of high-speed a/d sampling;
Step 2, high-speed a/d sampling form digital burst 1 of 2N-1 point and the digital burst 2 of 2N-1 point to measured signal 1 and measured signal 2 samplings under unified controlling of sampling, and are input to data buffer separately;
The digital sequence of 2N-1 point of the digital sequence of 2N-1 point of step 3, measured signal 1 and measured signal 2 by the data redundancy pre-service, is converted into the digital sequence of N point of measured signal 1 and the digital sequence of N point of measured signal 2 respectively;
The digital sequence of N point of step 4, measured signal 1 obtains comprising the frequency spectrum data of measured signal 1 phase information through the FFT conversion, and the gained phase data is the phase place of the digital sequence intermediate point of the 2N-1 point correspondence of measured signal 1 sampling.Equally, the digital sequence of the N of measured signal 2 point obtains comprising the frequency spectrum data of measured signal 2 phase informations through the FFT conversion, and the gained phase data is the phase place of the digital sequence intermediate point of the 2N-1 point correspondence of measured signal 2 samplings;
Step 5, measured signal 1 frequency spectrum data is carried out spectrum peak search, obtain the spectrum of measured signal 1 amplitude maximum, ask its imaginary part and the ratio of real part to calculate the corresponding accurate instantaneous phase value of the digital sequence intermediate point of 2N-1 point that arc tangent obtains measured signal 1 sampling again.Equally, measured signal 2 frequency spectrum datas are carried out spectrum peak search, obtain the spectrum of measured signal 2 amplitude maximums, ask its imaginary part and the ratio of real part to calculate the corresponding accurate instantaneous phase value of the digital sequence intermediate point of 2N-1 point that arc tangent obtains measured signal 2 samplings again; The difference of the instantaneous phase value of gained measured signal 1 and the instantaneous phase value of measured signal 2 is the phase differential between measured signal 1 and the measured signal 2.The instantaneous phase value of gained measured signal 1, the instantaneous phase value of measured signal 2 and measured signal 1 show after display process with the phase differential of measured signal 2;
Only comprise also in step 6, the described step 1 to 5 measured signal 1 or measured signal 2 handled that can obtain the accurate instantaneous phase value of single measured signal 1 or measured signal 2 this moment.
The unified controlling of sampling of each the high-speed a/d sampling in the described step 2 comprises sampling rate, begins to sample and finish to sample and control by systematic unity.
The data redundancy pre-service is that center both sides stacked compression become N point digital sequence with the sequence intermediate point with the digital sequence of 2N-1 point after windowing process in the described step 3.
All calculating are all finished at numeric field in the described step 3 to 5, utilize classical fft algorithm, are convenient to utilize digital processing chip realization fast.
By above technical scheme as can be known, measured signal is directly sampled by high-speed a/d behind signal condition and is formed Serial No. among the present invention, adopted the data redundancy treatment technology in the scheme, calculate the accurate instantaneous phase value of directly measuring measured signal 1 and measured signal 2 by FFT, thereby calculate phase differential easily.Need not do the square wave shaping to measured signal in technical scheme, this point and existing phase measurement scheme are different fully.Among the present invention all are calculated all at numeric field and are finished in by software algorithm, are convenient to adopt digital processing chip at a high speed to realize, also help reducing hardware complexity and system cost.
The advantage that the present invention compares with existing equipment is:
(1), can also provide the accurate instantaneous phase value of each measured signal except measuring the phase differential between the measured signal.
(2) adopt the data redundancy treatment technology, overcome the inaccurate shortcoming of phase place that causes because of frequency departure in the direct FFT calculating, thereby reduced control complexity the sample frequency of high-speed a/d sampling.
(3) adopt the data redundancy treatment technology with the digital sequence of the digital sequence boil down to of 2N-1 point N point, reduced the required operand of follow-up FFT conversion, and only need less sampled data just can obtain accurate phase value of measured signal and phase differential thereof, thereby realize at a high speed, high-precision phase measurement.
(4) calculated amount of the present invention is mainly finished at numeric field, and digital signal processing chip easy to use is realized.Reduce the complexity of system, made the manufacturing cost of equipment be in the allowed band, be convenient to adopt the chip of domestic and international main flow to realize.System software can upgrade according to using the needs of measuring.
Description of drawings
Figure 1 shows that and carry out fast phase meter structural representation of the present invention;
The phase differential analysis that Figure 2 shows that measured signal 1 and measured signal 2 is figure as a result;
The phase differential analysis that Figure 3 shows that the measured signal 1 that has noise and measured signal 2 is figure as a result;
Specific implementation
Basic thought of the present invention is: Fourier transform need be done conversion to the endless time-domain signal in theory, and this is difficult to accomplish in physics realization.Discrete Fourier transformation also can only be at limited long number word sequence in the practical application, and signal must be earlier through blocking.Because signal exists frequency departure and be subjected to harmonic wave or interference of noise between the truncation effect on the time domain, actual signal, there is very big error in the phase information of the measured signal that calculates by FFT.In traditional FFT spectrum analysis, have only by increasing the Serial No. length N to reach the purpose that reduces the phase difference measurement error, can increase the operand of fft algorithm so greatly, and poor effect.Measured signal in the present invention 1 and measured signal 2 obtain the Serial No. that the 2N-1 point comprises the measured signal phase information by the high-speed a/d sampling behind signal condition, N is the length that fft algorithm is carried out to be needed, and can set in advance.The sampling process of measured signal 1 and measured signal 2 is parallel processings, and is controlled by systematic unity.Thereby for fear of directly causing the energy leakage of signal spectrum to produce phase error to there being limit for length's sampling number word sequence to do the FFT computing, take elder generation that the digital sequence of 2N-1 point is done the redundant pre-service of data and be compressed into the digital sequence of N point, then the digital sequence of N point is carried out the FFT computing, can obtain the point-device instantaneous phase value of measured signal like this, thereby calculate the phase differential between the measured signal.Fast phase meter structural representation of the present invention as shown in Figure 1.Describe the phase difference measurement result of fast phase meter of the present invention in detail below by concrete exemplifying embodiment.
The phase differential analysis that is illustrated in figure 2 as measured signal 1 and measured signal 2 is figure as a result, in the exemplifying embodiment:
Measured signal 1 is: 1.0*cos (2 π * 48.1*t+50.123*pi/180);
Measured signal 2 is: 0.8*cos (2 π * 48.1*t+150.346*pi/180);
The frequency of measured signal is 48.1Hz, and in exemplifying embodiment, the computational length of getting FFT is N=512, satisfies the requirement of sampling thheorem, and the sample sequence of measured signal is long to be 2N-1=1023 point.The measured signal 1 that obtains after the pre-service of process data redundancy, FFT calculating, spectrum peak search and the arctangent computation and the instantaneous phase value and the phase differential of the two of measured signal 2 are as follows:
The instantaneous phase value of measured signal 1: 50.123 degree;
The instantaneous phase value of measured signal 2: 150.346 degree;
Phase differential between the measured signal is :-100.223 degree.
At the phase differential that does not have very accurately to measure under the condition of noise measured signal.
The phase differential analysis that is illustrated in figure 3 as the measured signal 1 that has noise and measured signal 2 is figure as a result, and is identical among measured signal and Fig. 2 in the exemplifying embodiment:
Measured signal 1 is: 1.0*cos (2 π * 48.1*t+50.123*pi/180);
Measured signal 2 is: 0.8*cos (2 π * 48.1*t+150.346*pi/180);
But increased white Gaussian noise in each measured signal, signal to noise ratio (S/N ratio) is not less than 15db.In exemplifying embodiment, the computational length of still getting FFT is N=512, satisfies the requirement of sampling thheorem, and the sample sequence of measured signal is long to be 2N-1=1023 point.The measured signal 1 that obtains after the pre-service of same process data redundancy, FFT calculating, spectrum peak search and the arctangent computation and the instantaneous phase value and the phase differential of the two of measured signal 2 are as follows:
The instantaneous phase value of measured signal 1: 50.2064 degree;
The instantaneous phase value of measured signal 2: 150.2815 degree;
Phase differential between the measured signal is :-100.0751 degree differ 0.1479 degree with theoretical value.Data presentation, under signal to noise ratio (S/N ratio) was not less than 15db, the measured signal 1 of measurement and the phase differential between the measured signal 2 and the relative error of theoretic phase difference value are about 0.15%, and be very accurate, can satisfy actual needs.
Claims (4)
1, a kind of fast phase meter comprises following processing procedure:
Step 11, measured signal 1 and measured signal 2 are input to the corresponding signal modulate circuit, and amplitude obtains conditioning, and little measured signal obtains amplifying, and big measured signal obtains decay, and the amplitude of signal is controlled near the full amplitude of high-speed a/d sampling;
Step 12, high-speed a/d sampling form digital burst 1 of 2N-1 point and the digital burst 2 of 2N-1 point to measured signal 1 and measured signal 2 samplings under unified controlling of sampling, and are input to data buffer separately;
The digital sequence of 2N-1 point of the digital sequence of 2N-1 point of step 13, measured signal 1 and measured signal 2 by the data redundancy pre-service, is converted into the digital sequence of N point of measured signal 1 and the digital sequence of N point of measured signal 2 respectively;
The digital sequence of N point of step 14, measured signal 1 obtains comprising the frequency spectrum data of measured signal 1 phase information through the FFT conversion, and the gained phase data is the phase place of the digital sequence intermediate point of the 2N-1 point correspondence of measured signal 1 sampling.Equally, the digital sequence of the N of measured signal 2 point obtains comprising the frequency spectrum data of measured signal 2 phase informations through the FFT conversion, and the gained phase data is the phase place of the digital sequence intermediate point of the 2N-1 point correspondence of measured signal 2 samplings;
Step 15, measured signal 1 frequency spectrum data is carried out spectrum peak search, obtain the spectrum of measured signal 1 amplitude maximum, ask its imaginary part and the ratio of real part to calculate the corresponding accurate instantaneous phase value of the digital sequence intermediate point of 2N-1 point that arc tangent obtains measured signal 1 sampling again.Equally, measured signal 2 frequency spectrum datas are carried out spectrum peak search, obtain the spectrum of measured signal 2 amplitude maximums, ask its imaginary part and the ratio of real part to calculate the corresponding accurate instantaneous phase value of the digital sequence intermediate point of 2N-1 point that arc tangent obtains measured signal 2 samplings again; The difference of the instantaneous phase value of gained measured signal 1 and the instantaneous phase value of measured signal 2 is the phase differential between measured signal 1 and the measured signal 2.The instantaneous phase value of gained measured signal 1, the instantaneous phase value of measured signal 2 and measured signal 1 show after display process with the phase differential of measured signal 2;
Only comprise also in step 16, the described step 11 to 15 measured signal 1 or measured signal 2 handled that can obtain the accurate instantaneous phase value of single measured signal 1 or measured signal 2 this moment.
2, a kind of fast phase meter according to claim 1 is characterized in that: the unified controlling of sampling of each the high-speed a/d sampling in the described step 12 comprises sampling rate, begins to sample and finish to sample and control by systematic unity.
3, a kind of fast phase meter according to claim 1 is characterized in that, the data redundancy pre-service is that center both sides stacked compression become N point digital sequence with the sequence intermediate point with the digital sequence of 2N-1 point after windowing process in the described step 13.
4, a kind of fast phase meter according to claim 1 is characterized in that, all calculating are all finished at numeric field in the described step 13 to 15, utilizes classical fft algorithm, is convenient to utilize digital processing chip realization fast.
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Cited By (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102095933A (en) * | 2010-12-07 | 2011-06-15 | 天津大学 | Phase test device and control method thereof |
| CN103217577A (en) * | 2013-04-15 | 2013-07-24 | 中国科学院力学研究所 | Digital phase meter and method for measuring high-frequency signal phase change |
| CN103454497A (en) * | 2013-09-10 | 2013-12-18 | 南京理工大学 | Phase difference measuring method based on improved windowing discrete Fourier transform |
| CN103892822A (en) * | 2012-12-26 | 2014-07-02 | 中国移动通信集团公司 | Electrocardiogram signal processing method and device |
| CN104360159A (en) * | 2014-11-19 | 2015-02-18 | 国网浙江余姚市供电公司 | Nuclear phase method and device |
| CN105890843A (en) * | 2016-04-18 | 2016-08-24 | 神华集团有限责任公司 | Dynamic balance method and dynamic balance device |
| CN106773614A (en) * | 2016-11-30 | 2017-05-31 | 中国科学院国家授时中心 | It is applied to the precision time interval measurement method and device of optical fiber time transmission |
| CN107483078A (en) * | 2017-07-26 | 2017-12-15 | 北京遥测技术研究所 | A kind of ship VDES system ASM systems receive frequency offset estimation implementation method |
| CN108662973A (en) * | 2018-04-04 | 2018-10-16 | 复旦大学 | Electromagnetic tracking system based on phase discriminating technology and method |
| CN110160577A (en) * | 2019-06-20 | 2019-08-23 | 广东工业大学 | A kind of angle displacement measurement method of incremental rotary encoder, device and equipment |
-
2008
- 2008-07-18 CN CNA2008101168536A patent/CN101320060A/en active Pending
Cited By (15)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102095933B (en) * | 2010-12-07 | 2012-11-07 | 天津大学 | Phase test device and control method thereof |
| CN102095933A (en) * | 2010-12-07 | 2011-06-15 | 天津大学 | Phase test device and control method thereof |
| CN103892822A (en) * | 2012-12-26 | 2014-07-02 | 中国移动通信集团公司 | Electrocardiogram signal processing method and device |
| CN103217577B (en) * | 2013-04-15 | 2015-07-29 | 中国科学院力学研究所 | Measure digital phasemeter and the method thereof of the change of radio-frequency signal phase place |
| CN103217577A (en) * | 2013-04-15 | 2013-07-24 | 中国科学院力学研究所 | Digital phase meter and method for measuring high-frequency signal phase change |
| CN103454497A (en) * | 2013-09-10 | 2013-12-18 | 南京理工大学 | Phase difference measuring method based on improved windowing discrete Fourier transform |
| CN103454497B (en) * | 2013-09-10 | 2016-09-21 | 南京理工大学 | Based on the method for measuring phase difference improving windowed DFT |
| CN104360159A (en) * | 2014-11-19 | 2015-02-18 | 国网浙江余姚市供电公司 | Nuclear phase method and device |
| CN105890843A (en) * | 2016-04-18 | 2016-08-24 | 神华集团有限责任公司 | Dynamic balance method and dynamic balance device |
| CN106773614A (en) * | 2016-11-30 | 2017-05-31 | 中国科学院国家授时中心 | It is applied to the precision time interval measurement method and device of optical fiber time transmission |
| CN107483078A (en) * | 2017-07-26 | 2017-12-15 | 北京遥测技术研究所 | A kind of ship VDES system ASM systems receive frequency offset estimation implementation method |
| CN107483078B (en) * | 2017-07-26 | 2019-08-09 | 北京遥测技术研究所 | A kind of ship VDES system ASM system reception frequency offset estimation implementation method |
| CN108662973A (en) * | 2018-04-04 | 2018-10-16 | 复旦大学 | Electromagnetic tracking system based on phase discriminating technology and method |
| CN108662973B (en) * | 2018-04-04 | 2020-07-03 | 复旦大学 | Electromagnetic tracking system and method based on phase discrimination technology |
| CN110160577A (en) * | 2019-06-20 | 2019-08-23 | 广东工业大学 | A kind of angle displacement measurement method of incremental rotary encoder, device and equipment |
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