CN101207403A - Broadband radio frequency front end of intermediate wave frequency band high dynamic range - Google Patents
Broadband radio frequency front end of intermediate wave frequency band high dynamic range Download PDFInfo
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Abstract
The invention provides a front end of broad band radio frequency in the medium-short wave frequency band high dynamic range, and relates to the front end of the broad band radio frequency in a medium-short wave frequency band spreading signal receiving system. The invention overcomes the shortcomings existing in the prior structure that the front end of the radio frequency has high noise coefficient, small dynamic range, and low image rejection. The front end of the radio frequency adopts a two-stage frequency conversion and low medium frequency outputting structure; a radio frequency signal enters into a medium-frequency baseband signal processing part after passing through a pre-amplification module, a frequency conversion module, a variable gain amplifier module, and a high-frequency amplifier module. The intermediate-frequency baseband processing part conducts digital demodulation under the drive of a clock signal. The variable gain amplifier module is realized by a digital method, and the dynamic requirement of the system can be ensured by three circuits of digital variable gain amplifier modules. Two circuits of local oscillation signals of the frequency conversion module and a clock signal provided to the digital baseband processing part are produced by a DDS plus PLL method. The PLL multiplies the frequency of a quartz oscillator outputted signal, the signal is inputted to three circuits of DDS after being driven by a buffer, and the signal output is realized.
Description
Technical field
The present invention relates to the broadband rf front end of intermediate waves frequency range spread-spectrum signal receiving system.
Background technology
The intermediate waves frequency range refers generally to the frequency range of 0.5MHz-30MHz, and intermediate waves communication utilizes ionosphere as transmission medium, and transmission range can reach thousands of kilometers.Because it is strong that intermediate waves communication has a survivability, the characteristics of long transmission distance are so its application is very extensive.At present, the intermediate waves frequency range is not used by the communication system of high dynamic range (as mobile communication).Spread spectrum communication system is meant after the frequency spectrum of information to be transmitted is expanded with certain specific spread spectrum function becomes broadband signal, sends in the channel and transmits, thereby utilize corresponding means its compression to be obtained the communication system of the information of transmitting again.Because the frequency spectrum of spread-spectrum signal is far longer than the bandwidth of raw information,, be difficult to monitored so often be submerged in below the interchannel noise through the signal behind the spread-spectrum.And spread spectrum function or frequency expansion sequence generally have pseudo-random characteristics, so spread spectrum communication system has extremely strong confidentiality.And radio-frequency front-end is an important step of intermediate waves spread spectrum system, directly has influence on operating distance, antijamming capability and the system bandwidth of spread spectrum system.
Modern receiver architecture generally comprises: image suppression receiver structure, zero intermediate frequency reciver structure, low intermediate frequency receiver structure and based on the digital if receiver structure of software radio.More than several structures separately pluses and minuses are all arranged: the image suppression receiver structure comprises that the Hartley mirror image suppresses structure and the Weaver mirror image suppresses structure, can eliminate image response and mirror image noise fully in theory, but, the Hartley mirror image need adopt fixed phase shifter because suppressing structure, and the fixed phase shifter in broadband is to be difficult to realize, therefore is not suitable for being applied to broadband receiver.And the Weaver mirror image suppresses the structure relative complex, and the gain of two path channels and phase mismatch degree are relatively large, and along with mismatch increases, mirror image inhibition degree can reduce in actual the use.The zero intermediate frequency reciver structure is to suppress the another kind of resulting structure that mirror image disturbs, and it is a baseband signal with the radiofrequency signal Direct Transform, therefore can eliminate mirror image fully and disturb.But also just because of the characteristics of this structure, the influence of dc shift and low-frequency noise is inevitably, and the radiation of local-oscillator leakage or low noise amplifier and leakage part just in time be down converted on the useful signal, thereby influences the overall performance of system.In order to eliminate the various adverse effects of zero intermediate frequency reciver structure, intermediate frequency can be chosen on the frequency of lower but non-zero low intermediate frequency receiver structure that Here it is.But this structure can bring mirror image to disturb again, so general low intermediate frequency receiver structure adopts the image-reject mixer and the multiphase filter of quadrature, the two all is to utilize signal and mirror image to disturb through the phase difference that exists after the mixing to distinguish signal and interference, but this structure is comparatively complicated, realizes acquiring a certain degree of difficulty.
Continuous development along with Digital Signal Processing, digital if receiver structure based on software radio is arisen at the historic moment, the digital if receiver structure of general software radio was finished functions such as filtering, amplification, gain controlling and frequency conversion before the A/D conversion, radiofrequency signal is transformed to intermediate frequency.Digital signal processor spare through special use after the A/D conversion carries out the Digital Down Convert processing, reduce streaming rate, IF (intermediate frequency) digital signal conversion is become baseband digital signal, delivering to general dsp again handles, realization is handled the relatively low digital baseband signal of various data transfer rates, finishes the realization of various anti-interference, anti-multipaths, adaptive equalization algorithm etc.; And function such as error correction FEC, reciprocal cross knit, deciphering.Though it is this structure has good versatility and opening, very high: as to require low-noise factor, high dynamic range, the inhibition of high mirror image and high linearity or the like for the requirement of radio-frequency front-end.The radio-frequency front-end of structure is difficult to reach above-mentioned requirements at present.
Summary of the invention
The purpose of this invention is to provide a kind of intermediate waves frequency range high dynamic range broadband rf front end, with the radio-frequency front-end noise factor height that overcomes existing structure, the shortcoming that dynamic range is little and the mirror image inhibition is low.It is by preliminary election amplification module 3, first order digital variable gain amplification module 4, first order frequency-variable module 5, second level digital variable gain amplification module 6, second level frequency-variable module 7, third level digital variable gain amplification module 8 and intermediate frequency amplification module 9 are formed, the signal output part of preliminary election amplification module 3 connects the signal input part of first order digital variable gain amplification module 4, the signal output part of first order digital variable gain amplification module 4 connects the signal input part of first order frequency-variable module 5, the signal output part of first order frequency-variable module 5 connects the signal input part of second level digital variable gain amplification module 6, the signal output part of second level digital variable gain amplification module 6 connects the signal input part of second level frequency-variable module 7, the signal output part of second level frequency-variable module 7 connects the signal input part of third level digital variable gain amplification module 8, and the signal output part of third level digital variable gain amplification module 8 connects the signal input part of intermediate frequency amplification module 9.
During work, the input of preliminary election amplification module 3 is connected on the antenna 1, with received RF signal by its inner low noise amplifier 3-1.The output of intermediate frequency amplification module 9 connects the input of baseband signal processing module 10.Radiofrequency signal enters into radio-frequency front-end from antenna 1, successively through preliminary election amplification module 3, first order variable gain amplification module 4 and the high intermediate-freuqncy signal of first order frequency-variable module 5 back outputs, high intermediate-freuqncy signal is again through second level variable gain amplification module 6 and second level frequency-variable module 7 back output Low Medium Frequency signals, again through entering into the Base-Band Processing part behind third level variable gain amplification module 8 and the intermediate frequency amplification module 9.Radio-frequency front-end down-converts to intermediate-freuqncy signal by two-stage frequency conversion with radiofrequency signal.Can realize the dynamic range that 100dB is above; The pre-low-noise amplifier of preliminary election amplification module has high-gain and low-noise factor, can reduce the noise factor of front end effectively; Two-stage frequency conversion can realize that higher mirror image suppresses, the requirement to gaining in the time of can satisfying the weak signal input simultaneously.The present invention has overcome the radio-frequency front-end noise factor height of existing structure, the shortcoming that dynamic range is little and the mirror image inhibition is low, has big promotional value.
Description of drawings
Fig. 1 is a structural representation of the present invention, Fig. 2 is the structural representation of execution mode two, Fig. 3 is the structural representation of first order digital variable gain amplification module 4, and Fig. 4 is based on the local oscillation signal generator of DDS+PLL pattern and the structural representation of base-band digital clock signal generating apparatus.
Embodiment
Embodiment one: specify present embodiment below in conjunction with Fig. 1.Present embodiment is by preliminary election amplification module 3, first order digital variable gain amplification module 4, first order frequency-variable module 5, second level digital variable gain amplification module 6, second level frequency-variable module 7, third level digital variable gain amplification module 8 and intermediate frequency amplification module 9 are formed, the signal output part of preliminary election amplification module 3 connects the signal input part of first order digital variable gain amplification module 4, the signal output part of first order digital variable gain amplification module 4 connects the signal input part of first order frequency-variable module 5, the signal output part of first order frequency-variable module 5 connects the signal input part of second level digital variable gain amplification module 6, the signal output part of second level digital variable gain amplification module 6 connects the signal input part of second level frequency-variable module 7, the signal output part of second level frequency-variable module 7 connects the signal input part of third level digital variable gain amplification module 8, and the signal output part of third level digital variable gain amplification module 8 connects the signal input part of intermediate frequency amplification module 9.
Embodiment two: specify present embodiment below in conjunction with Fig. 1,2,3 and 4.The difference of present embodiment and execution mode one is: preliminary election amplification module 3 comprises low noise amplifier 3-1, preselection filter 3-2 and radio frequency amplifier 3-3, the output of low noise amplifier 3-1 connects the input of preselection filter 3-2, and the output of preselection filter 3-2 connects the input of radio frequency amplifier 3-3.Preliminary election amplification module 3 is first order that radiofrequency signal enters front end, played filtering interfering, reduces system noise factor, amplified the effect of small-signal.The gain of preliminary election amplification module 3 is about 18dB.Calculate formula according to the cascade network noise factor, the multiplication factor of establishing cascade network n level is G
n, noise factor is F
n, the noise factor of cascade network is F
Σ, by formula (1) as can be known, the multiplication factor of prime and noise factor are to influence the system noise sonic system in the network
The key factor of number, promptly prime multiplication factor noise factor big more, the more little then system of noise factor is more little.Therefore the parameter designing of preliminary election amplification module directly has influence on the performance of whole system.Low noise amplifier 3-1 has lower noise factor and higher multiplication factor, meets the design principle of cascade network.The insertion loss of preselection filter also is the key factor that influences the radio-frequency front-end noise factor, so can suitably relax the Insertion Loss that bandwidth reduces filter.But preselection filter plays a part again to suppress image frequency, so its bandwidth again cannot be wide, need take moderate mode to satisfy both requirements simultaneously.Present embodiment adopts 5 rank Chebyshev LC band pass filters, and bandwidth is loosened to 1.5 times of signal bandwidth, can realize Insertion Loss less than 1.5dB, and mirror image suppresses to reach 80dB.
First order digital variable gain amplification module 4 comprises digital pad 4-1, fixed gain amplifier 4-2, data sampling module 4-3, control module 4-4 and π attenuator 4-5 by the FPGA realization, the input of digital pad 4-1 connects the output of preliminary election amplification module 3, the output of digital pad 4-1 connects the input of π attenuator 4-5, the output of π attenuator 4-5 is connected and fixed the input of gain amplifier 4-2, the output of fixed gain amplifier 4-2 connects the input of first order frequency-variable module 5 and the input of data sampling module 4-3, the output of data sampling module 4-3 connects the input of the control module 4-4 that is realized by FPGA, and the output of the control module 4-4 that is realized by FPGA connects the feedback signal input of digital pad 4-1.Fixed gain amplifier 4-2 guarantees the full gain of signal in the passage, thereby and digital pad 4-1 realizes digital Auto Gain control according to signal power size adjustment attenuation.The watt level of signal is determined by FPGA control data sampling module 4-3 sampling intermediate frequency output signal, the signal that data sampling module 4-3 samples carries out buffer-stored and does modulo operation in FPGA inside, the judgement that the data of delivery output detect through peak value obtains being sampled the maximum of signal, and then extrapolate the power of signal, the performance number of signal compares with the threshold value that sets in advance and obtains increasing the controlled quentity controlled variable signal of decaying or reducing to decay, thus the slip of control attenuation.Present embodiment adopts the mode compare one by one, utilizes the periodicity of carrier signal, and the peakedness ratio of having realized certain precision in less number of comparisons.Because the initial phase of data sampling module 4-3 sampling is at random, when sampling with fixed frequency, different initial phases can not all sample peak value, but can obtain the maximum that precision allows in the sampling at limited number of time under certain precision requires.The sample rate of system's reality is 6.1 times of signal frequency, and when number of comparisons was 54 times, trueness error was 0.037dBm, can satisfy the requirement of system fully.In real work when power when regulating the critical condition of decay, because fluctuation and hysteresis quality that peak value detects, so its output valve may make the multiplication factor of first order digital variable gain amplification module 4 constantly adjust in certain some fluctuation up and down, can't guarantee stably to work; Also saturated for fear of amplifier simultaneously, present embodiment has adopted the mode of multi-threshold judgement: the decay slippage that different thresholdings is corresponding different, the threshold value that also will set simultaneously when needing to increase decay is low, the threshold value height in the time of need reducing to decay.Can control overshoot effectively in this way, reduce fluctuation.The spread-spectrum signal dynamic range that receives in the application of reality is very big, so system adopts three grades of automatic gain controls, lay respectively at radio band, a Mid Frequency and two Mid Frequencies of system, this also is to consider that signal generally can only guarantee gain about 40dB a frequency range, and dynamic gain is assigned to different frequency ranges.The gain of first order digital variable gain amplification module 4 is about 0 to 30dB.Digital variable gain amplification module 6 in the second level is identical with operation principle with structure, the gain multiple of first order digital variable gain amplification module 4 with third level digital variable gain amplification module 8.
First order frequency-variable module 5 comprises frequency mixer 5-1, local oscillation signal generator 5-2, low pass filter 5-3 and amplifier 5-4, two inputs of frequency mixer 5-1 connect the output of first order digital variable gain amplification module 4 and the output of local oscillation signal generator 5-2 respectively, the output of frequency mixer 5-1 connects the input of low pass filter 5-3, and the output of low pass filter 5-3 connects the input of amplifier 5-4.Described low pass filter 5-3 selects crystal filter for use.The gain of amplifier 5-4 is about 22dB, about the output frequency 10.7MHz of first order frequency-variable module 5.
Local oscillation signal generator 5-2 is by crystal oscillator 5-2-1, phase-locked loop 5-2-2, buffering driver 5-2-3, one tunnel Direct Digital Frequency Synthesizers 5-2-4 and No. one low pass filter 5-2-5 form, the output of crystal oscillator 5-2-1 connects the input of phase-locked loop 5-2-2, the output of phase-locked loop 5-2-2 connects the input of buffering driver 5-2-3, the output of buffering driver 5-2-3 connects the input of one tunnel Direct Digital Frequency Synthesizers 5-2-4, and the output of one tunnel Direct Digital Frequency Synthesizers 5-2-4 connects the input of No. one low pass filter 5-2-5.The frequency 10MHz of crystal oscillator 5-2-1, the model of phase-locked loop 5-2-2 is ADF4001.The model of one tunnel Direct Digital Frequency Synthesizers 5-2-4 is AD9850, and this two all be the product of U.S. AD company.The output frequency of local oscillation signal generator 5-2 is about 13.5MHZ.
The local oscillation signal that is used for mixing in the second level frequency-variable module 7 can obtain from the second road output of the buffering driver 5-2-3 of local oscillation signal generator 5-2, promptly obtain the local oscillation signal that is used for mixing in the second level frequency-variable module 7, about the frequency 11.5MHZ of this local oscillation signal by two tunnel Direct Digital Frequency Synthesizers 7-16 and No. two low pass filter 7-17.Can also obtain the clock signal of follow-up baseband signal by three tunnel Direct Digital Frequency Synthesizers 16, No. three low pass filters 17 and level drive circuit 18 from the Third Road output of buffering driver 5-2-3.
Because the precision and the stability of system requirements frequency are all very high, so the local oscillation signal generator requires selected crystal oscillator to have and systems compliant or higher standard on device is chosen.High more then its output frequency of the precision of crystal oscillator output frequency and stability is just low more, for the selected crystal oscillator of present embodiment that requires that guarantees precision and stability needs frequency multiplication just can reach the frequency of local oscillation signal, so the local oscillation signal generator adopts DDS+PLL (being Direct Digital frequency synthesis+phase-locked loop) pattern.Because local oscillation signal does not need very fast frequency settling time and very wide frequency output area, therefore promptly adopt DDS signal excitation PLL pattern different with traditional DDS+PLL pattern with DDS signal interpolation PLL pattern, the present invention adopts the reference clock of the output signal of PLL as the DDS system, and DDS exports local oscillation signal according to frequency control word.Though this mode can not improve that PLL brings that phase noise and DDS brought was spuious, it is simple in structure, can satisfy the requirement of local oscillation signal to frequency and frequency resolution, also can not worsen the precision and the stability of frequency simultaneously.The radio-frequency front-end of present embodiment adopts two-stage frequency conversion, and first order frequency-variable module realization up-conversion is exported high intermediate-freuqncy signal, and second level frequency-variable module down-converts the signals to Low Medium Frequency output.This structure is simpler than the Hartley structure and the Weaver structure that suppress the mirror image interference, and mirror image disturbs and also can satisfy system requirements fully simultaneously.Low pass filter 5-3 in the first order frequency-variable module 5 adopts crystal filter, because preliminary election amplification module 3 is the suitable increase of bandwidth, so the signal after the frequency conversion must the strict guarantee bandwidth, otherwise can influence spreading gain.Though and crystal filter is compared with common LC filter bigger Insertion Loss is arranged, have that better squareness factor and band are outer to be suppressed, the requirement that can satisfy bandwidth fully and suppress to disturb.For one road stable and accurate clock being provided for the digital baseband processing section, the same with local oscillation signal, clock output requires to have higher frequency accuracy and stability, therefore can utilize the output of local oscillation signal source PLL to come the DDS of drive clock module, can obtain precision the same and stability with local oscillation signal.Because base band signal process partly requires clock to have the CMOS level, so the output of clock need be through overdrive circuit to satisfy the level requirement.
Intermediate frequency amplification module 9 comprises intermediate frequency amplifier 9-1 and frequency overlapped-resistable filter 9-2, and the input of intermediate frequency amplifier 9-1 connects the output of third level digital variable gain amplification module 8, and the output of intermediate frequency amplifier 9-1 connects the input of frequency overlapped-resistable filter 9-2.Because what the filter after first order mixing adopted is squareness factor crystal filter preferably, has guaranteed signal bandwidth preferably, therefore be provided with and can suitably relax in the parameter of final stage frequency overlapped-resistable filter, also can meet the demands.The gain of intermediate frequency amplification module 9 is about 22dB.
Intermediate waves frequency range high dynamic range broadband rf front end of the present invention has adopted Wideband Intermediate Frequency sampling software radio architecture, enter into intermediate frequency base band signal process part behind radiofrequency signal process preliminary election amplification module, frequency-variable module, variable gain amplification module and the intermediate frequency amplification module, intermediate frequency base band signal process part is done digital demodulation under the driving of clock module.The advantage of this structure is: the low noise amplifier of (1) preliminary election amplification module has high-gain and low-noise factor, can reduce the noise factor of front end effectively; (2) two-stage frequency conversion can realize that higher mirror image suppresses, the requirement to gaining in the time of can satisfying the weak signal input simultaneously; (3) local oscillation signal adopts DDS (Direct Digital frequency synthesis)+PLL (phase-locked loop) pattern can obtain higher frequency resolution and stability with the clock that offers the Digital Signal Processing part; (4) crystal filter has better squareness factor can satisfy the requirement of bandwidth better than common LC filter; The control of (5) three grades of automatic gains can distribute dynamic range effectively, and the control of digital automatic gain compare with simulated mode have control flexibly, characteristic of accurate.
Claims (6)
1. intermediate waves frequency range high dynamic range broadband rf front end, it is characterized in that it is by preliminary election amplification module (3), first order digital variable gain amplification module (4), first order frequency-variable module (5), second level digital variable gain amplification module (6), second level frequency-variable module (7), third level digital variable gain amplification module (8) and intermediate frequency amplification module (9) are formed, the signal output part of preliminary election amplification module (3) connects the signal input part of first order digital variable gain amplification module (4), the signal output part of first order digital variable gain amplification module (4) connects the signal input part of first order frequency-variable module (5), the signal output part of first order frequency-variable module (5) connects the signal input part of second level digital variable gain amplification module (6), the signal output part of second level digital variable gain amplification module (6) connects the signal input part of second level frequency-variable module (7), the signal output part of second level frequency-variable module (7) connects the signal input part of third level digital variable gain amplification module (8), and the signal output part of third level digital variable gain amplification module (8) connects the signal input part of intermediate frequency amplification module (9).
2. intermediate waves frequency range high dynamic range broadband rf front end according to claim 1, it is characterized in that preliminary election amplification module (3) comprises low noise amplifier (3-1), preselection filter (3-2) and radio frequency amplifier (3-3), the output of low noise amplifier (3-1) connects the input of preselection filter (3-2), and the output of preselection filter (3-2) connects the input of radio frequency amplifier (3-3).
3. intermediate waves frequency range high dynamic range broadband rf front end according to claim 1, it is characterized in that first order digital variable gain amplification module (4) comprises digital pad (4-1), fixed gain amplifier (4-2), data sampling module (4-3), control module (4-4) and π attenuator (4-5) by the FPGA realization, the input of digital pad (4-1) connects the output of preliminary election amplification module (3), the output of digital pad (4-1) connects the input of π attenuator (4-5), the output of π attenuator (4-5) is connected and fixed the input of gain amplifier (4-2), the output of fixed gain amplifier (4-2) connects the input of first order frequency-variable module (5) and the input of data sampling module (4-3), the output of data sampling module (4-3) connects the input of the control module (4-4) that is realized by FPGA, and the output of the control module (4-4) that is realized by FPGA connects the feedback signal input of digital pad (4-1).
4. intermediate waves frequency range high dynamic range broadband rf front end according to claim 1, it is characterized in that first order frequency-variable module (5) comprises frequency mixer (5-1), local oscillation signal generator (5-2), low pass filter (5-3) and amplifier (5-4), two inputs of frequency mixer (5-1) connect the output of first order digital variable gain amplification module (4) and the output of local oscillation signal generator (5-2) respectively, the output of frequency mixer (5-1) connects the input of low pass filter (5-3), and the output of low pass filter (5-3) connects the input of amplifier (5-4).
5. intermediate waves frequency range high dynamic range broadband rf front end according to claim 4, it is characterized in that local oscillation signal generator (5-2) is by crystal oscillator (5-2-1), phase-locked loop (5-2-2), buffering driver (5-2-3), one tunnel Direct Digital Frequency Synthesizers (5-2-4) and No. one low pass filter (5-2-5) are formed, the output of crystal oscillator (5-2-1) connects the input of phase-locked loop (5-2-2), the output of phase-locked loop (5-2-2) connects the input of buffering driver (5-2-3), an output of buffering driver (5-2-3) connects the input of one tunnel Direct Digital Frequency Synthesizers (5-2-4), and the output of one tunnel Direct Digital Frequency Synthesizers (5-2-4) connects the input of No. one low pass filter (5-2-5).
6. intermediate waves frequency range high dynamic range broadband rf front end according to claim 1, it is characterized in that intermediate frequency amplification module (9) comprises intermediate frequency amplifier (9-1) and frequency overlapped-resistable filter (9-2), the input of intermediate frequency amplifier (9-1) connects the output of third level digital variable gain amplification module (8), and the output of intermediate frequency amplifier (9-1) connects the input of frequency overlapped-resistable filter (9-2).
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| CN108254745A (en) * | 2018-03-16 | 2018-07-06 | 成都锦江电子系统工程有限公司 | The radio frequency microwave system of plant detections of radar is floated applied to water |
| CN109738872A (en) * | 2019-01-11 | 2019-05-10 | 上海英恒电子有限公司 | A kind of radar Cochannel interference method and device |
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