CN100431261C - Improved mixers with a plurality of local oscillators and systems based thereon - Google Patents

Abstract

Apparatus (40) for processing an input signal (SRF(t)) with a carrier frequency (omega RF)defining a desired band and at least a sideband being defined by a sideband frequency (nomega LO) that is higher than the carrier frequency (omega RF). The apparatus (40) comprises a main input (50) for receiving said input signal(SRF(t))and a first standard mixer (41) having a first mixer input (44), a first local oscillator input (47), and a first mixer output (A). The first mixer input (44) is connected to the main input (50) and the first local oscillator input (47) is connected to a source that provides a first local oscillator signal (LO1) having a frequency (omEga LO). This frequency (omega LO) is close to or equal to the carrier frequency (omega RF). The first standard mixer (41) performs a multiplication of the input signal (SRF(t)) and the first local oscillator signal (LO1) to provide a first output signal (SA(t))at the first mixer output (A). The apparatus (40) further comprises a second mixer (42) with a second mixer input (45), a second local oscillator input (48), and a second mixer output (B). The second mixer input (45) is connected to the main input (50) and the second local oscillator input (48) is connected to a source that provides a second local oscillator signal (LO2) with the sideband frequency (nomega LO). The second mixer (42) performs a multiplication of the input signal (SRF(t)) and the second local oscillator signal (LO2) to provide a second output signal (SB(t)) at the second mixer output (B). There are means for superpositioning (51) the first output signal (SA(t)) and the second output signal (SB(t)). The first local oscillator signal (LO1) and the second local oscillator signal (LO2) are square-wave signals.

Description

Has the improved frequency mixer of a plurality of local oscillators and based on its system

Technical field

The frequency mixer of (LO) that the present invention relates to have local oscillator and based on its system.More particularly, the present invention relates to be suitable for use in very much the frequency mixer of the parasitism inhibition (spurious reject) in the receiver, particularly radio frequency signal receiver.The invention still further relates to orthogonal mixer.

Background technology

Frequency mixer is that nearly all communication system is such as indispensable key element and important component piece in global system for mobile communications (GSM), Bluetooth system and the universal mobile telephone system (UMTS).Frequency mixer is used to realize having sent the frequency translation of signal (referring to information signal here).This frequency translation is by making two signals and may being that their harmonic wave multiplies each other and carries out.

In the receive path 10 of traditional receiver, for example use to have two visibly different passages, as shown in fig. 1: the down conversion mixers of radio frequency (RF) port one 1 and local oscillator (LO) port one 2.This frequency mixer 13 makes two signal multiplications that are applied to port one 1 and 12.The low pass filter (LPF) 14 of frequency mixer 13 outlet sides carries out filtering to signal after multiplication.In Fig. 2 A, show have first frequency band RF signal of (being called useful signal or effective band), wherein information signal is ω by having frequency _RFCarrier signal transmit.Except this first frequency band, also have other two parasitic frequency bands (being also referred to as parasitic frequency band or sideband) at upper frequency.The frequency spectrum of LO signal that is applied to port one 2 is shown in Fig. 2 B.This signal is transferred to the carrier frequency ω of effective RF signal _RFSimultaneously, this LO signal has high order harmonic component.In Fig. 2 B, 3 times and 5 subharmonic of this LO signal have been described.At the outlet side of filter 14, intermediate frequency (IF) signal comprises that useful signal adds the signal of parasitic frequency band.The signal that these three frequency bands have been shown in Fig. 2 C overlaps near zero.In this case, for receiver, can not from the information that transmits by parasitic frequency band, pick out the information that transmits by useful signal.

Frequency mixer promptly can be passive also can be active.Passive frequency mixer is simpler, reaches higher linearity and speed, but any gain is not provided.On the contrary, active mixer provides sizable gain, so that can reduce the noise effect that is caused by following stages.For this reason, passive frequency mixer is found to be applied in microwave and the base station circuitry, and active mixer is used in the RF system widely.

The LO signal of practical frequency mixer, no matter it is any type, all is square-wave signal.Be subjected to the control of square wave LO signal, when the transistor switch in the frequency mixer was conducting, the output A of passive frequency mixer was equal to RF input, and when this switch for by the time output A be zero.Therefore, the operation of passive frequency mixer can be counted as the square wave of the RF signal times of port one 1 with port one 2.

Active mixer, Gibert unit for example, use switching transistor that (for example MOS transistor) is used for current commutates, wherein use transconductance stage that the input voltage signal of RF port one 1 is converted to electric current, the switching transistor of the LO signal controlling by being subjected to LO port one 2 carries out rectification to this electric current then.In order circuit noise to be minimized and obtains best noise factor, need allow square wave LO signal conducting and by described switch discontinuously as far as possible suddenly with 50% duty factor.

In most of processing modes, the mixing operation of being considered is just imported with RF with sinusoidal LO signal times.Under this simplification situation, the output spectrum of frequency mixer only comprises two second order products: difference ω _RF-ω _LOWith and ω _RF+ ω _LOIn receiver, the former is an effective I F frequencies omega _RF, and the latter is suppressed by band pass filter after the frequency mixer 13 or low pass filter 14 (LPF).Just as will be described, this processing mode is too simple, is difficult to improve the performance of existing frequency mixer.

The detailed description of relevant frequency mixer, for example at Prentice Hall, 1998, provide in the book of " RF Microelectronics " (ISBN 0-13-887571-5) by name of BehzadRazavi.But the publication that also has many other relevant frequency mixers.

Because the LO signal of frequency mixer is that square wave is not a sine wave signal, therefore be that square wave rather than sine wave must be used for analyzing and design.When square-wave signal is applied to the LO port one 2 of frequency mixer 13, because the harmonic wave of LO signal, in the various cross products of the output A of frequency mixer generation RF and LO signal.Usually, even after some filtering, the RF input also not only comprises effective signal band, also comprises other undesired signal or parasitic signal.Parasitic signal mainly comes from other communication networks or other signal source, and still, they also should be possible from identical communication network.If ratio ξ=ω _CBW/ ω _LONot very little, then can this thing happens, ω wherein _CBWBe channel bandwidth.If it can show as ξ=2, then has the poorest a kind of situation, wherein owing to the odd harmonic of adjacent channel at LO, for example 3 ω _LO, 5 ω _LO... in be accurate, so adjacent channel becomes parasitic.After mixing, these parasitic signals and useful signal are similar to be arrived IF frequency band (comparison diagram 2C) by down converted, thereby destroys or even cover useful signal.Even parasitic signal that Here it is response yet leaves reason to improved obstruction to now frequency mixer.

Summary of the invention

Therefore the objective of the invention is to improve the electric current frequency mixer and based on its receiver.

Above-described obstruction is used in the parasitic frequency mixer that suppresses of the present invention of this description and requirement and eliminates.

Claimed according to frequency mixer of the present invention in claim 1.

Claimed various advantageous embodiments in claim 2 to 11.

Claimed the method according to this invention in claim 12.

Claimed various advantageous method in claim 13 to 22.

Frequency mixer according to the present invention is particularly suitable for use in the receiver.Claimed according to receiver of the present invention in claim 23.

Claimed a kind of favourable receiver embodiment in claim 24.

From immediate interest of the present invention is goodish performance, low-down cost, powerful competitiveness or the like.

The embodiment that other advantages of the present invention is detailed proposes.

Description of drawings

For the present invention more complete explanation and purpose and advantage, in conjunction with the accompanying drawings with reference to following description, in the accompanying drawing:

Fig. 1 is traditional RF frequency mixer.

Fig. 2 A describes the typical R F signal graph with two parasitic signals.

Fig. 2 B describes LO frequency and harmonic wave figure thereof.

Fig. 2 C is described in down converted (supposition zero IF) the destruction figure of the signal of three frequency bands afterwards.

Fig. 3 is the figure that describes as in conjunction with the employed square wave LO of frequency mixer according to the present invention signal.

Fig. 4 A describes according to the of the present invention first parasitic schematic block diagram that suppresses frequency mixer.

Fig. 4 B is the figure that describes as three square wave LO signals that use in conjunction with the frequency mixer among Fig. 4 A.

Fig. 5 is the figure that describes as other square wave LO signal that uses in conjunction with frequency mixer according to the present invention.

Fig. 6 A describes according to the of the present invention second parasitic schematic block diagram that suppresses frequency mixer.

Fig. 6 B is the figure that describes as three square wave LO signals that use in conjunction with the frequency mixer among Fig. 6 A.

Fig. 7 describes the schematic block diagram that suppresses frequency mixer according to trixenie of the present invention.

Fig. 8 is the schematic block diagram of describing according to receiver of the present invention.

Embodiment

The present invention is based on following principle.According to the existing cross product of the harmonic wave of LO square-wave signal in the frequency mixer research standard frequency mixer of the present invention, and produce these products exactly with deletion.For fear of " directly feedthrough ", the output of frequency mixer is detected as differential wave, promptly with respect to the signal of 0 symmetry.Therefore, square wave LO-1 and+switch between 1, as shown in Figure 3.

Among Fig. 3 the fourier series of waveform by:

$S_{\mathrm{LO}}\left(t\right)=\frac{4}{\mathrm{\π}}(\sin {\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{3}\sin 3{\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{5}\sin 5{\mathrm{\ω}}_{\mathrm{LO}}t+\·\·\·)---\left(1\right)$

Given.

ω wherein _LO=2 π/T, and T is the cycle of square wave.In formula (1), suppose 50% duty factor.For the parasitic frequency mixer that suppresses according to the present invention, the amplitude of n harmonic wave that importantly will note the LO signal is for less than amplitude n times of first-harmonic, as by shown in the formula (1).In order to simplify, at first the RF input is represented as S _RF(t).After multiplication, the result of ordering at frequency mixer A passes through:

$S_A\left(t\right)=\frac{4}{\mathrm{\π}}{S}_{\mathrm{RF}}\left(t\right)(\sin {\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{3}\sin 3{\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{5}\sin 5{\mathrm{\ω}}_{\mathrm{LO}}t+\·\·\·)---\left(2\right)$

Given.

Consider that below wherein RF is input as:

S _RF(t)＝Asin(ω _LOt+θ _A)+Bsin(3ω _LOt+θ _B)+Csin(5ω _LOt+θ _C)+…(3)

Situation.

First is carrier frequency ω _LOIn useful signal, the two or three is respectively at frequency 3 ω _LOWith 5 ω _LOTwo parasitic signals.After mixing, the signal that frequency mixer A is ordered is:

$S_A\left(t\right)=\frac{2}{\mathrm{\π}}(A\cos {\mathrm{\θ}}_A+\frac{B}{3}\cos {\mathrm{\θ}}_B+\frac{C}{5}\cos {\mathrm{\θ}}_C+\·\·\·)+\mathrm{HFT}---\left(4\right)$

Wherein HFT represents the high frequency item, and it can suppress by filtered device low pass filter afterwards.After filtering, first in the round parentheses is down converting signal, and second and the 3rd for because the 3rd and the 5th spurious response that harmonic wave causes of LO signal.In frequency domain, these two undesired will fall into IF frequency band (zero frequency of Fig. 2 C), thereby the signal to noise ratio (S/n) that reduces receiver also makes bit error rate (BER) worsen, because the bit that sends in effective band can not be distinguished mutually with the bit that sends in other frequency bands.Though before parasitic signal enters frequency mixer, will have certain filtering these parasitic signals that decay, unfortunately, the filter of any reality all only may provide the limited decay of these parasitic signals.Owing to lack the knowledge of relevant these parasitic signals, i.e. B, ξ _B, C, ξ _COr the like, up to now also without any remedying or solution can be used, and the parasitic signal response has become the obstacle of making great efforts to improve existing frequency mixer muchly in frequency mixer.Because the limited moving belt of filter, the parasitic signal that in general is centered around around the 3rd and the 5th harmonic wave of LO signal is the problem that bothers most, even and after filtering, they or even than also big at the useful signal of filter input end.

Here it is will describe and in the motivation of the present invention of this requirement.Use this novelty, creationary frequency mixer, can from frequency mixer output, eliminate the item of above-mentioned trouble fully.In order to simplify, but be without loss of generality, this creationary parasitic frequency mixer that suppresses will come open with two embodiment of the two or three that eliminate in formula (4) round parentheses.

It should be noted that in these embodiments that the method for describing can expand to eliminates other residual term and than event, but complexity will how undesired more inner modulation be long-pending increases owing to eliminating.

In Fig. 4 A, show according to the of the present invention first parasitic frequency mixer 40 that suppresses.Frequency mixer 40 comprises the frequency mixer 41,42 and 43 of three standards in this example.In general, if when eliminating undesired of first n-1 in formula (4) round parentheses, need n standard mixer altogether.RF signal S _RF(t) being applied in the RF port 44,45 and 46 of all three standard mixer 41,42 and 43, then is different for each standard mixer 41,42 with 43 LO signal.In other words, all standard mixer of frequency mixer 40 have a public input 50.The LO signal is respectively LO1, LO2 and LO3.Signal LO1 is applied to port 47, and signal LO2 is applied to port 48, and signal LO3 is applied to port 49.That is to say that each standard mixer 41,42,43 has independent LO port 47,48,49 respectively.By T1, T2 and T3 (comparison diagram 4B) expression signal LO1, in the cycle of LO2 and LO3, these signals must have following relation:

T2＝T1/3

T3＝T1/5(5)

And they also must have zero phase at t=0, shown in Fig. 4 B.This has guaranteed that the frequency of signal LO2 is three times of frequency of signal LO1, and the frequency of signal LO3 is five times of frequency of signal LO1, so that can simply realize.

According to the present invention, all LO signals all are square-wave signals.At present, formula (2) and (4) are still effective for the standard mixer 41 above among Fig. 4 A.Other two standard mixer 42 of ordering at B point and C and 43 result can similarly write respectively:

$S_B\left(t\right)=\frac{4}{\mathrm{\π}}{S}_{\mathrm{RF}}\left(t\right)(\sin 3{\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{3}\sin 9{\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{5}\sin 15{\mathrm{\ω}}_{\mathrm{LO}}t+\·\·\·)$

$S_C\left(t\right)=\frac{4}{\mathrm{\π}}{S}_{\mathrm{RF}}\left(t\right)(\sin 5{\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{3}\sin 15{\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{5}\sin 25{\mathrm{\ω}}_{\mathrm{LO}}t+\·\·\·)---\left(6\right)$

The RF input is given by formula (3) once more.In above-mentioned formula, produce by formula (3) replacement:

$S_B\left(t\right)=\frac{2}{\mathrm{\π}}B\cos {\mathrm{\θ}}_B+\mathrm{HFT}$

$S_C\left(t\right)=\frac{2}{\mathrm{\π}}C\cos {\mathrm{\θ}}_C+\mathrm{HFT}---\left(7\right)$

Below, if the output signal S of middle standard mixer 42 _B(t) by the factor 3 decay, the output signal S of following standard mixer 43 _C(t) by the factor 5 decay, and if output signal S _B(t) and S _C(t) then from the output signal S of top standard mixer 41 _A(t) deduct in, then the D S as a result of ordering _D(t) become:

$S_D\left(t\right)=\frac{2}{\mathrm{\π}}B\cos {\mathrm{\θ}}_A+\mathrm{HFT}---\left(8\right)$

Carry out subtraction, output signal S by adder 51 _B(t) and S _C(t) has negative sign.Can see that second and the 3rd is:

2Bcosθ _B/(3π)

With

2Ccosθ _C/(5π)

It is present in the output signal S of the top standard mixer that A orders _A(t) in (formula 4), the output signal S of the new frequency mixer 40 of ordering from D _D(t) complete obiteration, promptly they are eliminated fully or are suppressed.All higher frequency items (HFTs) can be suppressed by the low pass filter 52 of back, only are left useful signal in the output of frequency mixer 53:

$S_{\mathrm{IF}}\left(t\right)=\frac{2A}{\mathrm{\π}}\cos {\mathrm{\θ}}_A---\left(9\right)$

Therefore confirmed new frequency mixer 40, described in Fig. 4 A, suppressed parasitism fully, a kind of really parasitic frequency mixer that suppresses.

Frequency mixer according to first embodiment can be used in the mobile phone technology, for example reduces to intermediate frequency with radio frequency (RF) mobile telephone signal of heterodyne input.

According to another frequency mixer of the present invention, just except first frequency mixer, also has second frequency mixer, because this frequency mixer is designed to only eliminate 3 subharmonic.This frequency mixer is designed to handle the carrier frequency (ω with definition effective band _RF) and fall into the input signal S of sideband of 3 subharmonic of the first local oscillator signals LO1 _RF(t).This frequency mixer comprises and is used for receiving inputted signal S _RF(t) primary input and have first standard mixer of first frequency mixer input, the input of first local oscillator and the output of first frequency mixer.First frequency mixer input can be connected to primary input and the input of first local oscillator can be connected to provide have near or equal carrier frequency ω _RFFrequencies omega _LOThe signal source of the first local oscillator signals LO1.First standard mixer is carried out input signal S _RF(t) with the multiplication of the first local oscillator signals LO1, so that provide the first output signal S in the output of first frequency mixer _A(t).Its further comprise have second frequency mixer input, second standard mixer of the input of second local oscillator and the output of second frequency mixer.The input of second frequency mixer can be connected to primary input, and the input of second local oscillator can be connected to provide has frequency n ω _LOThe signal source of the second local oscillator signals LO2.Second standard mixer is carried out input signal S _RF(t) with the multiplication of the second local oscillator signals LO2, so that provide the second output signal S at second frequency mixer output B _B(t).This frequency mixer also comprises and is used for the coefficient-1/3 couple second output signal S _B(t) weighting is so that provide the device of second output signal of weighting.Provide an adder to the first output signal S _A(t) and second output signal-1/3 S of weighting _B(t) carry out addition.

The first local oscillator signals LO1 and the second local oscillator signals LO2 are square waves.

Below in conjunction with Fig. 5,6A and 6B another frequency mixer 60 according to the present invention is described.Frequency mixer 60 is called as orthogonal mixer, as what will illustrate in following paragraph.

In modern communications, orthogonal mixer is widely used in down-conversion frequencies or phase modulated signal.Orthogonal mixer comprises two identical standard mixer (being also referred to as in-phase channel or I channel and orthogonal channel or Q channel), the quadrature in phase of two LO signals.In order to reduce noise, two LO signals must be the square-wave signals with 50% duty factor.Shown in Figure 5 with the square-wave signal of square-wave signal quadrature among Fig. 3.Similarly, the fourier series of this waveform is given by the following formula:

$S_{\mathrm{LO}}\left(t\right)=\frac{4}{\mathrm{\π}}(\cos {\mathrm{\ω}}_{\mathrm{LO}}t-\frac{1}{3}\cos 3{\mathrm{\ω}}_{\mathrm{LO}}t+\frac{1}{5}\sin 5{\mathrm{\ω}}_{\mathrm{LO}}t-\·\·\·)---\left(10\right)$

Relatively formula (10) and formula (1), if two formula are cos function rather than sin function except (i) first-harmonic and harmonic wave, and (ii) the 2nd, 4,6 ... the symbol of item is for negative outer identical.Therefore, can obtain to be orthogonal to Fig. 4 A the frequency mixer that the parasitism of its counterpart suppresses by the coefficient that uses the LO signal and from-1/3 to+1/3 shown in Fig. 6 B to change second standard mixer 62 simply.

This frequency mixer promptly can be that the back (for example has the suitable coefficient of application, under the situation of first embodiment-1/3, or in quadrature embodiment+1/3) standard mixer of discrete cell in the multiplication, also can be the specific frequency mixer that can use like this, wherein carry out input signal S _RF(t) with the multiplication of LO signal (for example LO1) so that in this multiplication, use separately coefficient.In accompanying drawing 4A and 6A, the discrete cell 54,55 and 74,75 that is designed to use coefficient has separately been described respectively.It will also be appreciated that the LO signal follows coefficient separately to take place.In this case, the LO2 signal for example should have coefficient-1/3.

The down converted of (RF) input signal that receives is provided in conjunction with the frequency mixer of the present invention's use.This down converted realizes that by multiply operation the input signal that wherein receives (RF) multiply by local oscillator signals (LO).In order to realize this mixing function, local oscillator (LO) signal the carrier frequency of the effective band of input or near propagation.Difference between LO signal and the frequency input signal causes intermediate frequency (IF).

According to the present invention, promptly can have and the as many independent local oscillations source of standard mixer (for example three frequency mixers and three LO signal sources), can have a generator that a plurality of oscillator signals are provided to combinational logic again.This combinational logic makes up a plurality of oscillator signals to produce effective local oscillator signals.

The embodiment that wherein uses two local oscillations sources has been described in Fig. 7.Frequency mixer 90 comprises two standard mixer as the part of unit 91.Have two local oscillators 93 and 94.First local oscillator, 93 output signal LO1, second local oscillator, 94 output signal LO2 are described in Fig. 7.In addition, frequency mixer 90 has the receiving inputted signal of being used for S _RF(t) input 92 and the output 95 that is used to provide output signal.

The radio frequency signal receiver 80 that comprises according to another kind of configuration of the present invention has been described among Fig. 8.Receiver 80 comprises frequency mixer 84, provide the generator 86 of a plurality of oscillator signals (to provide three different oscillator signals in this example, therefore 87 have three connections from generator 86 to combinational logic), and combinational logic 87, to obtain required LO signal LO1, LO2 and LO3.Receiver 80 comprises that also there is the antenna 81 of front end band pass filters 82 back.This filter 82 can be used for filtering undesired " image " signal before arriving frequency mixer 84.There is the low noise amplifier 83 (LNA) that the RF signal that is received is provided amplification front end band pass filters 83 back.Because frequency mixer 84 is directly followed low noise amplifier 83, therefore determine the performance of whole receiver system 80 just like this.At the output D of frequency mixer 84, for example low pass filter of filter 85-can be set.

Data processing unit 89 can be connected to the output 88 of filter 85.Data processing unit 89 is carried out the reprocessing of information signal (preferably digital signal), and this information signal transmits in the effective band of accepting by antenna 81.Data processing unit 89 can comprise the microprocessor or Digital Signal Processing (DSP) machine of some form.Receiver system 80 can be the part of the RX path of GSM, bluetooth or UMTS mobile phone for example.

Mixer 40 and 60 in conjunction with Fig. 4 A and 6A is described and illustrates, and adding an additional frequency mixer among the figure provides in traditional frequency mixer and suppress because a harmonic wave of LO signal cause the ability of parasitic signal more.In general, add n additional frequency mixer in the conventional mixer of Fig. 1, synthetic frequency mixer is suppressed around n parasitic signal of the harmonic wave of n altogether of LO signal.

As desired, the multiparasitization signal becomes complicated more to synthetic frequency mixer owing to suppressing more.Because it is complicated more that this circuit becomes, and can't so be easy to find suitable multiplier when checking, as above, except passing through solution formula.On the other hand, the high order harmonic component of square wave has lower amplitude, and the parasitic signal of upper frequency can suppress by filtered fully device.This just requires trade off (trade-off).Parasitic signal depends on around several subharmonic up to the LO signal to be used and concrete situation.

Yet it is reasonable and suitable that the embodiment that believes the frequency mixer among Fig. 4 A and the 6A uses for great majority.This is owing to following at least two reasons: at first, because n harmonic wave of LO signal, the cross product and the n that fall into the IF frequency band are inversely proportional to.Secondly, because its frequency is further from the centre frequency of band pass filter, or the corner frequency of low pass filter separates, and the logical or low pass filter of band can provide the more decay to signal.Similar with parasitic signal, the input noise frequency spectrum in the IF frequency band of the odd harmonic of LO signal falls into the forbidden band after mixing.Fortunately be that they still can be suppressed by the creationary parasitic frequency mixer that suppresses.

An advantage of the invention is that described frequency mixer can realize as integrated circuit at an easy rate.Therefore it is relatively cheap that they make meeting.CMOS technology limit is fit to this purpose.This creationary principle for example can be applied in the fully-integrated CMOS receiver.But can make field-effect transistors too.

The present invention can be applied to the heterodyne system radio frequency receiver.Be suitable for multiple frequency mixer of the present invention and have many potential practical applications, comprise integrated circuit and module and other wireless communications products of being used for radio frequency receiver.They for example use in single sideband mixer and quadrature demodulator and demodulator.

Being appreciated that for simplification that the of the present invention various features of describing in the scope of embodiment independently also can be combined among the single embodiment provides.On the contrary, also can separate for each feature of the present invention of in the scope of single embodiment, describing for simplicity or in any suitable sub-portfolio, provide.

The preferred embodiments of the present invention are set forth in drawing and description, though used specific term, the only technology on general describing significance is used in the description that provides like this, and is not in order to limit.

Claims (25)

1. be used to handle input signal (S _RF(t)) device (40; 60; 80; 90), this input signal has the carrier frequency (ω of definition effective band _RF) and at least one have the carrier frequency of being higher than (ω _RF) sideband frequency (n ω _RF) sideband, this device (40; 60; 80; 90) comprising:

-be used to receive described input signal (S _RF(t)) primary input (50; 70; 79; 92);

-have first frequency mixer to import (44; 64), the input of first local oscillator (47; 67) and first frequency mixer (41 of first frequency mixer output (A); 61), the input of first local oscillator (47; 67) can be connected to provide and have the carrier frequency of equaling (ω _RF) frequency (ω _LO) the signal source (86 of first local oscillator signals (LO1); 87; 93), first frequency mixer (41; 61) carry out described input signal (S _RF(t)) with the multiplication of described first local oscillator signals (LO1), so that provide the first output signal (S in first frequency mixer output (A) _A(t)),

-at least one has second frequency mixer input (45; 65), the input of second local oscillator (48; 68) and second frequency mixer (42 of second frequency mixer output (B); 62), the input of second local oscillator (48; 68) can be connected to (the n ω that has frequency is provided _LO) the signal source (86 of second local oscillator signals (LO2); 87; 94), frequency (the n ω of second local oscillator signals (LO2) wherein _LO) be different from the frequency (ω of first local oscillator signals (LO1) _LO), second frequency mixer (42; 62) carry out described input signal (S _RF(t)) with the multiplication of second local oscillator signals (LO2), so that provide the second output signal (S in second frequency mixer output (B) _B(t)),

It is characterized in that,

First and second frequency mixers input (44; 64; 45; 65) can be connected to primary input (50; 70; 79; 92),

-be used to carry out the first output signal (S _AAnd the second output signal (S (t)) _BThe device of stack (t)),

First local oscillator signals (LO1) and second local oscillator signals (LO2) are square-wave signal, wherein second frequency mixer (42; 62) carrying out described input signal (S _RFDuring (t)) with the multiplication of described second local oscillator signals (LO2), according to sideband frequency (n ω _RF), use negative or positive coefficient (1/3;-1/3; 1/n;-1/n).

2. device (40 as claimed in claim 1; 60; 80; 90), wherein be used to carry out first output signal and the second output signal (S _BThe device of stack (t)) is implemented as an adder (51; 71).

3. device (40 as claimed in claim 1; 60; 80; 90), wherein effective band is transmitted in and has carrier frequency (ω _RF) carrier signal on the information signal modulated.

4. device (40 as claimed in claim 3; 60; 80; 90), wherein said information signal is a numerical data.

5. as any one described device (40 among the claim 1-4; 60; 80; 90), sideband frequency (n ω wherein _LO) be carrier frequency (ω _RF) odd harmonic.

6. as any one described device (40 among the claim 1-4; 60; 80; 90), further be included in this device (40; 60; 80; 90) outlet side low pass filter (LPF; 52; 72; 85).

7. as any one described device (40 among the claim 1-4; 60; 80; 90), wherein for fear of direct feedthrough, this device (40; 60; 80; 90) output is detected as differential wave.

8. as any one described device (40 among the claim 1-4; 60; 80; 90), wherein the cycle (T2) of the cycle (T1) of first local oscillator signals (LO1) and second local oscillator signals (LO2) has following relation: T2=T1/3.

9. as any one described device (40 among the claim 1-4; 60; 80; 90), wherein first local oscillator signals (LO1) and second local oscillator signals (LO2) have zero phase at the t=0 place.

10. as any one described device (60 among the claim 1-4; 80; 90), wherein first local oscillator signals (LO1) and second local oscillator signals (LO2) have quadrature phase.

11. as any one described device (40 among the claim 1-4; 60; 80; 90), wherein said square wave has 50% duty factor.

12. be used to handle input signal (S _RF(t)) method, this input signal have the carrier frequency (ω of definition effective band _RF) and at least one the definition sideband sideband frequency (n ω _RF), sideband frequency (n ω wherein _RF) be higher than carrier frequency (ω _RF), this method may further comprise the steps:

-receive described input signal (S _RF(t)),

-provide to have the carrier frequency of equaling (ω _RF) frequency (ω _LO) first local oscillator signals (LO1),

-carry out described input signal (S _RF(t)) with the multiplication of described first local oscillator signals (LO1), so that the first output signal (S is provided _A(t)),

-(the n ω that has frequency is provided _LO) second local oscillator signals (LO2), frequency (the n ω of second local oscillator signals (LO2) wherein _LO) be different from the frequency (ω of first local oscillator signals (LO1) _LO),

-carry out described input signal (S _RF(t)) with the multiplication of described second local oscillator signals (LO2), so that the second output signal (S is provided _B(t)),

It is characterized in that,

-with input signal (S _RF(t)) directly be provided to the frequency mixer (41 of carrying out multiplication; 42),

-execution first output signal (the S _AAnd the second output signal (S (t)) _B(t)) stack,

Wherein first local oscillator signals (LO1) and second local oscillator signals (LO2) are square-wave signal,

Carrying out described input signal (S _RFDuring (t)) with the multiplication of described second local oscillator signals (LO2), according to sideband frequency (n ω _RF), use negative or positive coefficient (1/3;-1/3; 1/n;-1/n).

13. method as claimed in claim 12 is wherein by an adder (51; 71) carry out stack.

14. method as claimed in claim 12, wherein effective band is transmitted in and has carrier frequency (ω _RF) carrier signal on the information signal modulated.

15. method as claimed in claim 14, wherein said information signal is a numerical data.

16. as any one described method among the claim 12-15, wherein sideband frequency (n ω _RF) be carrier frequency (ω _RF) odd harmonic.

17. as any one described method among the claim 12-15, a low pass filter (LPF who uses at outlet side; 52; 72; 85).

18. as any one described method among the claim 12-15, wherein said output is detected as differential wave.

19. as any one described method among the claim 12-15, wherein the cycle (T1) of first local oscillator signals (LO1) has following relation: T2=T1/3 with the cycle (T2) of second local oscillator signals (LO2).

20. as any one described method among the claim 12-15, wherein first local oscillator signals (LO1) and second local oscillator signals (LO2) have zero phase at the t=0 place.

21. as any one described method among the claim 12-15, wherein first local oscillator signals (LO1) and second local oscillator signals (LO2) have quadrature phase.

22. as any one described method among the claim 12-15, wherein said square wave has 50% duty factor.

23. receiver comprises according to any one described device (40 among the claim 1-11; 60; 80; 90), described device (40; 60; 80; 90) be to handle input signal (S _RF(t)) to be converted into low frequency medium frequency signal (S _IFThe part of a series of circuit (t)) (82,83,85,89).

24. receiver as claimed in claim 23, described receiver are the heterodyne system radio frequency receivers.

25. receiver as claimed in claim 23 is the part of global mobile communication (GSM) system, Bluetooth system or universal mobile telephone system.

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