CA2372134C - Motor control apparatus - Google Patents
Motor control apparatus Download PDFInfo
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- CA2372134C CA2372134C CA002372134A CA2372134A CA2372134C CA 2372134 C CA2372134 C CA 2372134C CA 002372134 A CA002372134 A CA 002372134A CA 2372134 A CA2372134 A CA 2372134A CA 2372134 C CA2372134 C CA 2372134C
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- axis
- term component
- armature
- current
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/08—Arrangements for controlling the speed or torque of a single motor
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/28—Arrangements for controlling current
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/22—Current control, e.g. using a current control loop
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Control Of Ac Motors In General (AREA)
- Control Of Motors That Do Not Use Commutators (AREA)
Abstract
An integral term component generating unit 21 integrates a d-axis current difference AId and a q-axis current difference .DELTA.Iq using an integral gain Ki which is determined to stabilize a system where the d-axis current difference .DELTA.Id and the q-axis current difference .DELTA.Iq are multiplied by the integral gain Ki, integrated, and inputted, with respect to a steady gain M which approximates, including proportional gains Kp, the steady input-to-output relationship of a motor 2 to which the voltage applied to a d-axis armature and the voltage applied to a q-axis armature are inputted and from which the current flowing through the d-axis armature and the current flowing through the q-axis armature are outputted, thereby a d-axis integral term component Vd i which is an integral term component of a d-axis command voltage Vd_c and a q-axis integral term component Vq_i which is an integral term component of a q-axis command voltage Vq_c are generated.
Description
MOTOR CONTROL APPARATUS
BACKGROUND OF THE INVENTION
Field of the Invention:
The present invention relates to a motor control apparatus for controlling currents flowing through the ar-matures of a DC brushless motor according to a feedback control process.
Description of the Related Art:
One conventional method of controlling a DC
brushless motor employs a vector control process (hereinaf-ter referred to as "dq control process") whicli converts a 3-phase (U, V, W) DC brushless motor into an equivalent circuit having a q-axis armature on a q-axis which is aligned with the direction of magnetic fluxes of field sys-tems on the rotor of the motor and a d-axis ai:mature on a d-axis which extends perpendicularly to the q--axis.
A conventional motor control apparatus for car-rying out the dq control process is arranged as shown in FIG. 3 of the accompanying drawings. As shown in FIG. 3, a motor control apparatus 50 serves to control currents flow-ing through the armatures of a DC servomotor 51, and has a U-phase current sensor 52 for detecting a current IU s flowing through a U-phase armature of the DC servomotor 51 and a W-phase current sensor 53 for detecting a current IW_s flowing through a W-phase armature of the DC servomo-tor 51.
The currents IU_s, IW_s and an electric angle 0 of the rotor of the motor 51 which is detected by a posi-tion detecting sensor (resolver or the like) 54 are sup-plied to a 3-phase/dq converter 55, which outputs an actual current Ia s flowing through the d-axis armature and an ac-tual current Iq_s flowing through the q-axis armature.
The motor control apparatus 50 is supplied with a command value Id c for the current flowing through the d-axis armature and a comenand value Iq_c for the current flowing through the q-axis armature. A first subtractor 56 calculates the difference AId between the command value Id c and the actual current Id s, and a second subtractor 57 calculates the difference AIq between the command value Iq_c and the actual current Iq_s.
A first PI processor 58 and a second PI proces-sor 59 perform a proportional and integral (Px) process to reduce the differences AId, AIq, and calculate a command value Vd_c for the voltage applied to the d-axis armature and a command value Vq_c for the voltage applied to the q-axis armature, respectively. The command values Vd c, Vq_c are supplied to a dq/3-phase converter 60, which converts them into comstand values VU_c, VV c, VW c for the voltages applied to the three-phase (U, V, W) armatures. A power drive unit 61 applies voltages according to the command values VU c, VV c, VW c to the three-phase armatures of the motor 51.
The process carried out by the first PI proces-sor 58 and the second PI processor 59 is expressed by the following equation (1):
Vd KPAId +KiJ'Qiddt +cvi~e Vq s KpAIq +Ki f Wqdt . . . (1) where Vd: the voltage applied to the d-axis armature, Vq:
the voltage applied to the q-axis armature, Kp: the propor-tional gain, Ki: integral gain, w: the angular velocity of the motor, and Re: the induced voltage constant.
In the applications of many motors,, sufficient stability and responsiveness is achieved by the feedback control process of the above general proportional and inte-gral control system. However, when the motor is operated at high rotational speeds, the motor may operate unstably or the control responsiveness may become insufficient under the control of the general proportional and integral con-trol system.
The primary reason for the above drawbacks is considered to reside in that since the state equation of the proportional and integral control system is given as the following equation (2), when the motor operates at a high rotational speed, interference between the d- and q-axes increases due to the induced voltage generated depend-ing on the angular velocity w of the motor, causing the control system to respond in a vibrating fashion.
d d = r~ c~ ~ Id ~ Id = dt dt Iq `-ur ~ - i Iq ~ f'Iq = dt ...~2~
r 0 Id c Ld 0 r ~I c Lq where Id: the current flowing through the d-axis armature, Iqa the current flowing through the q-axis armature, Lds the inductance of the d-axis armature, Lq: the inductance of the q-axis armature, and r: the resistance of the d-axis armature and the q-axis armature.
SUMARY OF THE INVENTION
According to the present invention, there is provided a motor control apparatus for converting a DC
brushless motor into an equivalent circuit having a q-axis armature on a q-axis which is aligned with the direction of magnetic fluxes of field systems of the motor and a d-axis armature on a d-axis which extends perpendicularly to the q-axis, comprising current detecting means for detecting currents flowing through armatures of the motor, actual current calculating means for calculating a q-axis actual current flowing through the q-axis armature and a d-axis actual current flowing through the d-axis armature from the currents detected by the current detecting means, and cur-rent,difference calculating means for calculating a q-axis current difference between a q-axis command current which is a command value for the current flowing through the q-axis armature and the q-axis actual current and a d-axis current difference between a d-axis command current which is a command value for the current flowing through the d-axis armature and the d-axis actual current, means for gen-erating a d-axis command voltage which is a command value for the voltage applied to the d-axis armature and a q-axis command voltage which is a command value for the voltage applied to the q-axis armature in order toreduce the d-axis current difference and the q-axis current difference, and means for controlling the currents flowing through the armatures of the motor depending on the d-axis command voltage and the q-axis command voltage.
The motor control apparatus comprises propor-tional term component generating means for carrying out a proportional process to multiply the d-axis current differ-ence and the q-axis current difference by respective prede-termined proportional gains to generate a d-axis propor-tional term component which is a proportional term compo-nent of the d-axis command voltage and a q-axis proportion-al term component which is a proportional terna component of the q-axis command voltage, integral term component gen-erating means for effecting an integrating process on the d-axis current difference and the q-axis current difference based on a predetermined integral gain to generate a d-axis integral term component which is an integral term component of the d-axis command voltage and a q-axis integral term component which is an integral term component of the q-axis command voltage, and command voltage generating means for generating the d-axis command voltage depending on the sum of the d-axis proportional term component and the d-axis integral tena component, and the q-axis command voltage de-pending on the sum of the q-axis proportional term compo-nent and the q-axis integral term component, means for set-ting the integral gain to stabilize a system in which the d-axis current difference and the q-axis current difference are multiplexed, integrated, and inputted, with respect to a steady gain which approximates, including the proportion-al gains, the steady input-to-output relationship of the motor to which the voltage applied to the d-axis armature and the voltage applied to the q-axis armature are inputted and from which the current flowing through the d-axis arma-ture and the current flowing through the q-axis armature are outputted.
With the above arrangement, the proportional term component generating means generates the d-axis pro-portional term component and the q-axis proportional term component. In order to increase the ability of the d-axis actual current to follow the d-axis command current and the ability of the q-axis actual current to follow the q-axis command current to control the motor stably when the motor operates at a high rotational speed, it is necessary to in-crease the proportional gain thereby to increase the re-sponse of the motor to the d-axis command voltage and the q-axis command voltage.
However, only increasing the proportional gain poses a problem in that the motor tends to vibrate in its operation. According to the present invention, therefore, the integral term component generating means generates the d-axis integral term component and the q-axis integral term component in order to alleviate the above shortcoming.
Specifically, the integral term component gen-erating means performs the integrating process based on the integral gain that is set to stabilize the system in which the d-axis current difference and the q-axis current dif-ference are multiplexed, integrated, and inputted, with re-spect to the steady gain which approximates, including the proportional gains, the steady input-to-output relationship between the voltage applied to the d-axis armature and the voltage applied to the q-axis armature and the current flowing through the d-axis armature and the current flowing through the q-axis armature, thereby generating the d-axis integral term component and the q-axis integral term compo-nent.
Stability of the integrating process using the steady gain will be described below with reference to FIG.
BACKGROUND OF THE INVENTION
Field of the Invention:
The present invention relates to a motor control apparatus for controlling currents flowing through the ar-matures of a DC brushless motor according to a feedback control process.
Description of the Related Art:
One conventional method of controlling a DC
brushless motor employs a vector control process (hereinaf-ter referred to as "dq control process") whicli converts a 3-phase (U, V, W) DC brushless motor into an equivalent circuit having a q-axis armature on a q-axis which is aligned with the direction of magnetic fluxes of field sys-tems on the rotor of the motor and a d-axis ai:mature on a d-axis which extends perpendicularly to the q--axis.
A conventional motor control apparatus for car-rying out the dq control process is arranged as shown in FIG. 3 of the accompanying drawings. As shown in FIG. 3, a motor control apparatus 50 serves to control currents flow-ing through the armatures of a DC servomotor 51, and has a U-phase current sensor 52 for detecting a current IU s flowing through a U-phase armature of the DC servomotor 51 and a W-phase current sensor 53 for detecting a current IW_s flowing through a W-phase armature of the DC servomo-tor 51.
The currents IU_s, IW_s and an electric angle 0 of the rotor of the motor 51 which is detected by a posi-tion detecting sensor (resolver or the like) 54 are sup-plied to a 3-phase/dq converter 55, which outputs an actual current Ia s flowing through the d-axis armature and an ac-tual current Iq_s flowing through the q-axis armature.
The motor control apparatus 50 is supplied with a command value Id c for the current flowing through the d-axis armature and a comenand value Iq_c for the current flowing through the q-axis armature. A first subtractor 56 calculates the difference AId between the command value Id c and the actual current Id s, and a second subtractor 57 calculates the difference AIq between the command value Iq_c and the actual current Iq_s.
A first PI processor 58 and a second PI proces-sor 59 perform a proportional and integral (Px) process to reduce the differences AId, AIq, and calculate a command value Vd_c for the voltage applied to the d-axis armature and a command value Vq_c for the voltage applied to the q-axis armature, respectively. The command values Vd c, Vq_c are supplied to a dq/3-phase converter 60, which converts them into comstand values VU_c, VV c, VW c for the voltages applied to the three-phase (U, V, W) armatures. A power drive unit 61 applies voltages according to the command values VU c, VV c, VW c to the three-phase armatures of the motor 51.
The process carried out by the first PI proces-sor 58 and the second PI processor 59 is expressed by the following equation (1):
Vd KPAId +KiJ'Qiddt +cvi~e Vq s KpAIq +Ki f Wqdt . . . (1) where Vd: the voltage applied to the d-axis armature, Vq:
the voltage applied to the q-axis armature, Kp: the propor-tional gain, Ki: integral gain, w: the angular velocity of the motor, and Re: the induced voltage constant.
In the applications of many motors,, sufficient stability and responsiveness is achieved by the feedback control process of the above general proportional and inte-gral control system. However, when the motor is operated at high rotational speeds, the motor may operate unstably or the control responsiveness may become insufficient under the control of the general proportional and integral con-trol system.
The primary reason for the above drawbacks is considered to reside in that since the state equation of the proportional and integral control system is given as the following equation (2), when the motor operates at a high rotational speed, interference between the d- and q-axes increases due to the induced voltage generated depend-ing on the angular velocity w of the motor, causing the control system to respond in a vibrating fashion.
d d = r~ c~ ~ Id ~ Id = dt dt Iq `-ur ~ - i Iq ~ f'Iq = dt ...~2~
r 0 Id c Ld 0 r ~I c Lq where Id: the current flowing through the d-axis armature, Iqa the current flowing through the q-axis armature, Lds the inductance of the d-axis armature, Lq: the inductance of the q-axis armature, and r: the resistance of the d-axis armature and the q-axis armature.
SUMARY OF THE INVENTION
According to the present invention, there is provided a motor control apparatus for converting a DC
brushless motor into an equivalent circuit having a q-axis armature on a q-axis which is aligned with the direction of magnetic fluxes of field systems of the motor and a d-axis armature on a d-axis which extends perpendicularly to the q-axis, comprising current detecting means for detecting currents flowing through armatures of the motor, actual current calculating means for calculating a q-axis actual current flowing through the q-axis armature and a d-axis actual current flowing through the d-axis armature from the currents detected by the current detecting means, and cur-rent,difference calculating means for calculating a q-axis current difference between a q-axis command current which is a command value for the current flowing through the q-axis armature and the q-axis actual current and a d-axis current difference between a d-axis command current which is a command value for the current flowing through the d-axis armature and the d-axis actual current, means for gen-erating a d-axis command voltage which is a command value for the voltage applied to the d-axis armature and a q-axis command voltage which is a command value for the voltage applied to the q-axis armature in order toreduce the d-axis current difference and the q-axis current difference, and means for controlling the currents flowing through the armatures of the motor depending on the d-axis command voltage and the q-axis command voltage.
The motor control apparatus comprises propor-tional term component generating means for carrying out a proportional process to multiply the d-axis current differ-ence and the q-axis current difference by respective prede-termined proportional gains to generate a d-axis propor-tional term component which is a proportional term compo-nent of the d-axis command voltage and a q-axis proportion-al term component which is a proportional terna component of the q-axis command voltage, integral term component gen-erating means for effecting an integrating process on the d-axis current difference and the q-axis current difference based on a predetermined integral gain to generate a d-axis integral term component which is an integral term component of the d-axis command voltage and a q-axis integral term component which is an integral term component of the q-axis command voltage, and command voltage generating means for generating the d-axis command voltage depending on the sum of the d-axis proportional term component and the d-axis integral tena component, and the q-axis command voltage de-pending on the sum of the q-axis proportional term compo-nent and the q-axis integral term component, means for set-ting the integral gain to stabilize a system in which the d-axis current difference and the q-axis current difference are multiplexed, integrated, and inputted, with respect to a steady gain which approximates, including the proportion-al gains, the steady input-to-output relationship of the motor to which the voltage applied to the d-axis armature and the voltage applied to the q-axis armature are inputted and from which the current flowing through the d-axis arma-ture and the current flowing through the q-axis armature are outputted.
With the above arrangement, the proportional term component generating means generates the d-axis pro-portional term component and the q-axis proportional term component. In order to increase the ability of the d-axis actual current to follow the d-axis command current and the ability of the q-axis actual current to follow the q-axis command current to control the motor stably when the motor operates at a high rotational speed, it is necessary to in-crease the proportional gain thereby to increase the re-sponse of the motor to the d-axis command voltage and the q-axis command voltage.
However, only increasing the proportional gain poses a problem in that the motor tends to vibrate in its operation. According to the present invention, therefore, the integral term component generating means generates the d-axis integral term component and the q-axis integral term component in order to alleviate the above shortcoming.
Specifically, the integral term component gen-erating means performs the integrating process based on the integral gain that is set to stabilize the system in which the d-axis current difference and the q-axis current dif-ference are multiplexed, integrated, and inputted, with re-spect to the steady gain which approximates, including the proportional gains, the steady input-to-output relationship between the voltage applied to the d-axis armature and the voltage applied to the q-axis armature and the current flowing through the d-axis armature and the current flowing through the q-axis armature, thereby generating the d-axis integral term component and the q-axis integral term compo-nent.
Stability of the integrating process using the steady gain will be described below with reference to FIG.
2(a). A steady gain M which approximates the input-to-output relationship of a system (2-input, 2-output system) to which a voltage Vd applied to a d-axis armature and a voltage Vq applied to a q-axis armature are inputted and from which a current Id flowing through the d-axis armature and a current Iq flowing through the q-axis armature are outputted, is multiplied by the difference AId between a command current value Id c for the d-axis armature and the current Id and the difference AIq between a command current value Iq_c for the q-axis armature and the current Iq, and the products are integrated (Ki, l!s) to generate a voltage Vd applied to the d-axis armature and a voltage Vq applied to the q-axis armature. In this case, variations in the differences AId, AIq are suppressed by the integrating process.
Therefore, if an integral gain Ki for stabiliz-ing an output produced by multiplying the steady gain M by the current differences AId, AIq and integrating products is used, the system ranging from a subtractor 30 to the output of the steady gain M is stabilized as a, whole, al-lowing the current Id to follow the command current value Id_c stably and also allowing the current Iq to follow the command current value Iq_c stably.
Thus, the integral term component generating means performs the integrating process based on the inte-gral gain determined to stabilize the system based on the steady gain, thereby generating the d-axis integral term component and the q-axis integral term component. The d-axis command voltage is generated based on the sum of the d-axis integral term component and the d-axis proportional term component, and the q-axis command voltage is generated based on the sum of the q-axis integral term component and the q-axis proportional term component. In this manner, the system approximated by the steady gain is stabilized to control the motor stably with a good follow-up capability even when the motor operates at high rotational speeds.
Since the electric response of the motor is very quick, if the motor follows the d-axis command voltage and the q-axis command voltage at all times, then the steady gain in the steady state of the system can be expressed by the equation (3) shown below, and the input-to-output rela-tionship can be expressed by the equation (4) shown below.
The integral gain can be determined using the steady gain expressed by the equation (3).
r + Kp -wLq -' M a.d r+Kp .. . (3) where M: the steady gain, r: the resistance of the d-axis armature and the q-axis armature, Kp: the proportional gains, Lds the inductance of the d-axis armature, and Lqs the inductance of the q-axis armature;
Therefore, if an integral gain Ki for stabiliz-ing an output produced by multiplying the steady gain M by the current differences AId, AIq and integrating products is used, the system ranging from a subtractor 30 to the output of the steady gain M is stabilized as a, whole, al-lowing the current Id to follow the command current value Id_c stably and also allowing the current Iq to follow the command current value Iq_c stably.
Thus, the integral term component generating means performs the integrating process based on the inte-gral gain determined to stabilize the system based on the steady gain, thereby generating the d-axis integral term component and the q-axis integral term component. The d-axis command voltage is generated based on the sum of the d-axis integral term component and the d-axis proportional term component, and the q-axis command voltage is generated based on the sum of the q-axis integral term component and the q-axis proportional term component. In this manner, the system approximated by the steady gain is stabilized to control the motor stably with a good follow-up capability even when the motor operates at high rotational speeds.
Since the electric response of the motor is very quick, if the motor follows the d-axis command voltage and the q-axis command voltage at all times, then the steady gain in the steady state of the system can be expressed by the equation (3) shown below, and the input-to-output rela-tionship can be expressed by the equation (4) shown below.
The integral gain can be determined using the steady gain expressed by the equation (3).
r + Kp -wLq -' M a.d r+Kp .. . (3) where M: the steady gain, r: the resistance of the d-axis armature and the q-axis armature, Kp: the proportional gains, Lds the inductance of the d-axis armature, and Lqs the inductance of the q-axis armature;
r +Kp , d Vd Iq l [ I r coLd r + Kp [vq 0 M Vq ...( 4) where Id: the current flowing through the d-axis armature, Iq: the current flowing through the q-axis armature, w: the angular velocity of the motor, Vd: the voltage applied to the d-axis armature, and Vq: the voltage applied to the q-axis armature.
Inasmuch as the steady gain M expressed by the equation (3) is a regular matrix, if the integral gain is established according to the equation (5) shown below using an arbitrary stable matrix S, then the state equation of an output (voltage) x according to an integrating process us-ing the steady gain is indicated as the equation (6) shown below. The stable matrix is a matrix where the real parts of intrinsic values are all negative. If the system matrix (-KiM) in the equation (6) is a stable matrix, then the state of the output x according to the above state equation is stable.
C
Ki = -detM =M''S . kll ~1 k1 = = . ( 5 ) where Ki: the integral gain, and S: a predetermined arbi-trary stable matrix.
d x=-KiM=x=-detM=M'SM=x ... (6) at Since detM > 0 and M-1SM is a stable matrix in the equation (6), if the integral gain is deteicmined ac-cording to the equation (5), then the system matrix (-KiM) is also stable matrix, stabilizing the state of the output x.
The integral term component generating means calculates the d-axis integral term component according to the equation (7) shown below and the q-axis integral term component according to the equation (8) shown below in the integrating process based on the integral gain.
Vd i = f (k11 = AId +k12= AIq)dt = = = ( 7 ) Vq i = f (k21 = did + k22 = DIq)dt -(8) where Vd_i: the d-axis integral term component, Vq_i: the q-axis integral term component, and kil, k12, k21, k22: ma-trix elements of the integral gain Ki defined by the equa-tion (5).
If the integral gain is established according to the equation (9) shown below using an arbitra=y positive definite matrix Q, then the state equation of an output (voltage) x according to an integrating process using the steady gain M expressed by the equation (3) is indicated as the equation (10) shown below. The positive definite ma-trix is a symmetrical real matrix where the intrinsic val-ues are all positive. If the system matrix (-MTQM) in the .equation (10) is a stable matrix, then the state of the output x is stable.
Inasmuch as the steady gain M expressed by the equation (3) is a regular matrix, if the integral gain is established according to the equation (5) shown below using an arbitrary stable matrix S, then the state equation of an output (voltage) x according to an integrating process us-ing the steady gain is indicated as the equation (6) shown below. The stable matrix is a matrix where the real parts of intrinsic values are all negative. If the system matrix (-KiM) in the equation (6) is a stable matrix, then the state of the output x according to the above state equation is stable.
C
Ki = -detM =M''S . kll ~1 k1 = = . ( 5 ) where Ki: the integral gain, and S: a predetermined arbi-trary stable matrix.
d x=-KiM=x=-detM=M'SM=x ... (6) at Since detM > 0 and M-1SM is a stable matrix in the equation (6), if the integral gain is deteicmined ac-cording to the equation (5), then the system matrix (-KiM) is also stable matrix, stabilizing the state of the output x.
The integral term component generating means calculates the d-axis integral term component according to the equation (7) shown below and the q-axis integral term component according to the equation (8) shown below in the integrating process based on the integral gain.
Vd i = f (k11 = AId +k12= AIq)dt = = = ( 7 ) Vq i = f (k21 = did + k22 = DIq)dt -(8) where Vd_i: the d-axis integral term component, Vq_i: the q-axis integral term component, and kil, k12, k21, k22: ma-trix elements of the integral gain Ki defined by the equa-tion (5).
If the integral gain is established according to the equation (9) shown below using an arbitra=y positive definite matrix Q, then the state equation of an output (voltage) x according to an integrating process using the steady gain M expressed by the equation (3) is indicated as the equation (10) shown below. The positive definite ma-trix is a symmetrical real matrix where the intrinsic val-ues are all positive. If the system matrix (-MTQM) in the .equation (10) is a stable matrix, then the state of the output x is stable.
( Ki MTQ ^ k11 k1 k21 k2~
...( g) where Q: a predetermined arbitrary positive definite ma-trix.
~x=-KiM-x=-MTQM=x ... (10) In the equation (10), because (MrQM) is a posi-tive definite matrix, (-M'FQM) is a stable matrix. There-fore, the state of the output x can be stabilized by deter-mining the integral gain according to the equation (9).
The integral term component generating means calculates the d-axis integral term component according to the equation (7) and the q-axis integral term component ac-cording to the equation (8), using the integral gain Ki de-termined by the equation (9) in the integratir-g process based on the integral gain.
The above and other objects, features, and ad-vantages of the present invention will become apparent from the following description when taken in conjunction with the accompanying drawings which illustrate pre:ferred embod-iments of the present invention by way of exauLple.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a block diagram of a motor control ap-.
paratus according to the present invention;
FIGS. 2(a), 2(b), and 2(c) are block diagrams showing various processes of determining an integral gain used in the motor control apparatus shown in FIG. 1; and FIG. 3 is a block diagram of a conventional mo-tor control apparatus.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
As shown in FIG. 1, a motor control apparatus 1 according to the present invention converts a 3-phase (U, V, W) DC brushless motor 2 (hereinafter referred to as "mo-tor 2") into an equivalent circuit having a q.-axis armature on a q-axis which is aligned with the direction of magnetic fluxes of field systems on the rotor (not shown) of the mo-tor 2 and a d-axis armature on a d-axis which extends per-pendicularly to the q-axis, and controls currents flowing through the armatures of the motor 2 accordinci to a feed-back control process.
The motor control apparatus 1 has a U-phase cur-rent sensor 3 (corresponding to a current detecting means) for detecting a current IU_s flowing through a. U-phase ar-mature of the motor 2, a W-phase current sensor 4 (corre-sponding to a current detecting means) for detecting a cur-rent IW s flowing through a W-phase armature of the motor 2, and a position detecting sensor 5 for detecting an elec-tric angle 0 of the rotor (not shown) of the motor 2.
The motor control apparatus 1 also has a 3-phase/dq converter 6 (corresponding to an actual current calculating means) for being supplied with the current IU s, the current IW_s, and the electric angle 0 and out-putting a d-axis actual current Id_s flowing through the d-axis armature and a q-axis actual current Iq_s flowing through the q-axis armature, a first subtractor 7 for sub-tracting the d-axis actual current Id_s from a d-axis com-mand value Id_c for the current flowing through the d-axis armature thereby to calculate a d-axis current difference AId which is the difference between the d-axis actual cur-rent Id_s and the d-axis command value Id c, and a second subtractor 8 for subtracting the q-axis actual current Iq_s from a q-axis command value Iq_c for the current flowing through the q-axis armature thereby to calculate a q-axis current difference AIq which is the difference between the q-axis actual current Iq_s and the q-axis command value Iq_c.
The motor control apparatus 1 further includes a d-axis proportional term component generator 9 for multi-plying the d-axis current difference AId by a proportional gain Kp thereby to generate a d-axis proportional term com-ponent Vd_p, a q-axis proportional term component generator for multiplying the q-axis current difference AIq by the proportional gain Kp thereby to generate a q-axis propor-tional term component Vd q, an integral term component gen-erator 21 (corresponding to an integral term component gen-erating means) for being supplied with the d-axis current difference AId and the q-axis current difference AIq and generating a d-axis integral term component Vd._i and a q-axis integral term component Vq_i, and a noninterference processor 18 for outputting noninterference processing term components Vd_n, Vq_n to cancel out the effeci: of speed electromotive forces that interfere with each other between the d-axis and the q-axis.
The first subtractor 7 and the second subtractor 8 jointly make up a current difference calculating means, and the d-axis proportional term component geinerator 9 and the q-axis proportional term component generator 10 jointly make up a proportional term component generating means.
The motor control apparatus 1 has ,3 first adder 14 for adding the d-axis proportional term component Vd_p, the d-axis integral term component Vd_i, and the noninter-ference processing term component Vd n for thEs d-axis to each other to calculate a d-axis comm and voltage Vd c which is a command value for the voltage applied to the d-axis armature, and a second adder 15 for adding the q-axis pro-portional term component Vqp, the q-axis integral term component Vq_i, and the noninterference processing term component Vc,Ln for the q-axis to each other to calculate a q-axis command voltage Vq_c which is a command value for the voltage applied to the q-axis armature.
The motor control apparatus 1 also has a dq/3-phase converter 16 for converting the d-axis command volt-age Vd_c, the q-axis command voltage Vq_c, and the electri-cal angle 0 into three-phase command voltages VU_c, VV c, VW_c and outputting the three-phase command voltages VU_c, VV_c, vW c, a power drive unit 17 for being supplied with the three-phase command voltages VU c, VV c, VW c and out-putting frequency-variable voltages depending on the three-phase command voltages VU_c, VV_c, VW c to the armatures of the motor 2, and an angular velocity processor 19 for dif-ferentiating (d/dt) the detected signal of the electrical angle 0 from the position detecting sensor 5 to calculate an angular velocity co of the motor 2 and outputting the an-gular velocity c,u to the noninterference processor 18.
The first adder 14 and the second adder 15 jointly make up a command voltage generating means.
The integral term component generator 21 ap-proximates, with a steady gain M according to the equation (4), the steady input-to-output relationship of the motor 2 which is represented by a block 20 including the d-axis proportional term component generator 9 and the q-axis pro-portional term component generator 10, for being supplied with the voltage Vd applied to the d-axis armature and the voltage Vq applied to the q-axis armature and outputting the current Id flowing through the d-axis armature and the current iq flowing through the q-axis armature.
specifically, the integral term component gen-erator 21 approximates the input-to-output relationship with the steady gain M including the proportional gain xp as a parameter and also including the angular velocity w, the resistance r of the d-axis armature and the q-axis ar-mature, the inductance Ld of the d-axis armature, and the inductance Lp of the q-axis armature.
Then, the integral term component generator 21 effects an integrating process on the set of the d-axis current difference DId and the q-axis current difference AIq using, as an integral gain Ri, a gain for stabilizing the state of the output when the steady gain M, the d-axis current difference AId, and the q-axis current difference AIq are multiplied, integrated, and fed back.
Specifically, as indicated by the equation (11) shown below, the integral term component generator 21 mul-tiplies the set (AId, AIq)r of the d-axis current differ-ence AId and the q-axis current difference AIq by the inte-gral gain Ri, as indicated by 11 in FIG. 1, generates the d-axis integral term component Vd_i from the product ac-cording to the equation (7) as indicated by 12 in FIG. 1, and generates the q-axis integral term component Vq_i from the product according to the equation (8) as indicated by 13 in FIG. 1.
]K3. (DId ~ (k21 k22~dI
~ ~
11=AId+k12=AI = = = (11) ~21=t1Id+k22=AI
~
The d-axis integral term component Vd_i generat-ed by the integral term component generator 21 is added to the d-axis proportional term component Vd_p by the first adder 14, and the q-axis integral term component Vq_i gen-erated by the integral term component generator 21 is added to the q-axis proportional term component Vq_p by the sec-ond adder 15. The first and second adders.14, 15 input the d-axis command voltage Vd_c and the q-axis coinmand voltage Vq_c represented by the equation (12) shown below to the dq/3-phase converter 16.
r d c Kpdid + f'(k11 - AId +k12= bIq)dt - cvI,qlq.s +mIKc .
q _~ KpdIq + f(k21 = QId +k22 = DIq)dt -,;c:I.dId s ===(12) where w: the angular velocity of the motor 5, Ld: the in-ductance of the d-axis armature, Lq: the inductance of the q-axis armature, and Ke: the induced voltage constant.
The third term of the first line on the right side of the equation (12) represents the noninterference processing term component Vd n for the d-axis, whereas the third term of the second line on the right sicle of the equation (12) represents the noninterference processing term component Vq_n for the q-axis.
As described above, the integral term component generator 21 performs an integral process based on the in-tegral gain Ri which is determined to stabilize the output state when the steady gain N including the proportional gain Kp according to the equation (3) as a parameter, the d-axis current difference AId, and the q-axis current dif-ference DIq are multiplied, the product is irategrated, and the integrated product is fed back.
By generating the d-axis integral term component Vd_i which is an integral term component of the d-axis com-mand voltage Vd_c and the q-axis integral term component Vq_i which is an integral term component of the q-axis com-mand voltage Vq_c according to the above integral process, it is possible to bring the d-axis actual current Id s into stable conformity with the d-axis command current Id c and also bring the q-axis actual current Iq_s into stable con-formity with the q-axis command current Iq_c even if the proportional gain Kp is increased to increase the respon-siveness of the motor 2.
As a result, variations in the voltage Vd ap-plied to the d-axis armature and the voltage Vq applied to the q-axis armature and increases in the d-axis current difference AId and the q-axis current differeiace Aiq, both of which variations and increases are caused when the pro-portional gain is increased to operate the moitor at a high rotational speed in the conventional general PI control process, are suppressed, making it possible to control the motor with small variations in the voltages Vd, Vq and good responsiveness even when the motor 2 operates at high rota-tional speeds.
In the present embodiment, the integral term component generator 21 uses the integral gain Ki determined according to the equation (5). However, the product of a transposed matrix MT of the steady gain M determined by the equation (9) and a predetermined arbitrary positive defi-nite matrix Q may be used as the integral gain Ki.
The feedback control system shown in FIG. 2(a) may be considered in the form of the state feedback of the integrator as shown in FIG. 2(b), and the theory of an op-tim,um regulator may be applied to determine tlfie integral gain Ki. In this case, the state equation of an object to be controlled is expressed as the following equation (13):
dta-Ax+Bu (13) ...
y=cX
where A = 0, B = M, C- I.
Therefore, the Riccati's equation can be simpli-fied into the Liapunov's equation expressed by the equation (14) shown below, and the Liapunov's equation can be solved for its solution P to determine the integral grain Ki ac-cording to the equation (15) shown below.
-PMR''MrP + Q = 0 = = = (14 ) where Q, P, R: arbitrary positive definite matrixes.
Ki = -R-1MTP = = = (15) where R, P: arbitrary positive definite matrixes.
Furthermore, because the stability remains un-changed if the system shown in FIG. 2(b) is converted into a system shown FIG. 2(c), the integral gain Ki may be de-termined according to the following equation (16):
Ki = -M'' = M(M''R''MTP)M'1 ...
MR "'MTPM'~ ( ) = -detM = M'' {detM 1 M( where P, R: arbitrary positive definite matrixes.
Inasmuch as (-MR-IMTP) is stable due to the posi-tive definiteness of R, P, the above equation (16) has the term within the braces replaced with the stable matrix S
according to the equation (5). Alternatively,. the stable matrix S may be determined using the solution of the opti-mum regulator according to the equation (16).
Although certain preferred embodiments of the present invention have been shown and described in detail, it should be understood that various changes and modifica-tions may be made therein without departing from the scope of the appended claims.
...( g) where Q: a predetermined arbitrary positive definite ma-trix.
~x=-KiM-x=-MTQM=x ... (10) In the equation (10), because (MrQM) is a posi-tive definite matrix, (-M'FQM) is a stable matrix. There-fore, the state of the output x can be stabilized by deter-mining the integral gain according to the equation (9).
The integral term component generating means calculates the d-axis integral term component according to the equation (7) and the q-axis integral term component ac-cording to the equation (8), using the integral gain Ki de-termined by the equation (9) in the integratir-g process based on the integral gain.
The above and other objects, features, and ad-vantages of the present invention will become apparent from the following description when taken in conjunction with the accompanying drawings which illustrate pre:ferred embod-iments of the present invention by way of exauLple.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a block diagram of a motor control ap-.
paratus according to the present invention;
FIGS. 2(a), 2(b), and 2(c) are block diagrams showing various processes of determining an integral gain used in the motor control apparatus shown in FIG. 1; and FIG. 3 is a block diagram of a conventional mo-tor control apparatus.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
As shown in FIG. 1, a motor control apparatus 1 according to the present invention converts a 3-phase (U, V, W) DC brushless motor 2 (hereinafter referred to as "mo-tor 2") into an equivalent circuit having a q.-axis armature on a q-axis which is aligned with the direction of magnetic fluxes of field systems on the rotor (not shown) of the mo-tor 2 and a d-axis armature on a d-axis which extends per-pendicularly to the q-axis, and controls currents flowing through the armatures of the motor 2 accordinci to a feed-back control process.
The motor control apparatus 1 has a U-phase cur-rent sensor 3 (corresponding to a current detecting means) for detecting a current IU_s flowing through a. U-phase ar-mature of the motor 2, a W-phase current sensor 4 (corre-sponding to a current detecting means) for detecting a cur-rent IW s flowing through a W-phase armature of the motor 2, and a position detecting sensor 5 for detecting an elec-tric angle 0 of the rotor (not shown) of the motor 2.
The motor control apparatus 1 also has a 3-phase/dq converter 6 (corresponding to an actual current calculating means) for being supplied with the current IU s, the current IW_s, and the electric angle 0 and out-putting a d-axis actual current Id_s flowing through the d-axis armature and a q-axis actual current Iq_s flowing through the q-axis armature, a first subtractor 7 for sub-tracting the d-axis actual current Id_s from a d-axis com-mand value Id_c for the current flowing through the d-axis armature thereby to calculate a d-axis current difference AId which is the difference between the d-axis actual cur-rent Id_s and the d-axis command value Id c, and a second subtractor 8 for subtracting the q-axis actual current Iq_s from a q-axis command value Iq_c for the current flowing through the q-axis armature thereby to calculate a q-axis current difference AIq which is the difference between the q-axis actual current Iq_s and the q-axis command value Iq_c.
The motor control apparatus 1 further includes a d-axis proportional term component generator 9 for multi-plying the d-axis current difference AId by a proportional gain Kp thereby to generate a d-axis proportional term com-ponent Vd_p, a q-axis proportional term component generator for multiplying the q-axis current difference AIq by the proportional gain Kp thereby to generate a q-axis propor-tional term component Vd q, an integral term component gen-erator 21 (corresponding to an integral term component gen-erating means) for being supplied with the d-axis current difference AId and the q-axis current difference AIq and generating a d-axis integral term component Vd._i and a q-axis integral term component Vq_i, and a noninterference processor 18 for outputting noninterference processing term components Vd_n, Vq_n to cancel out the effeci: of speed electromotive forces that interfere with each other between the d-axis and the q-axis.
The first subtractor 7 and the second subtractor 8 jointly make up a current difference calculating means, and the d-axis proportional term component geinerator 9 and the q-axis proportional term component generator 10 jointly make up a proportional term component generating means.
The motor control apparatus 1 has ,3 first adder 14 for adding the d-axis proportional term component Vd_p, the d-axis integral term component Vd_i, and the noninter-ference processing term component Vd n for thEs d-axis to each other to calculate a d-axis comm and voltage Vd c which is a command value for the voltage applied to the d-axis armature, and a second adder 15 for adding the q-axis pro-portional term component Vqp, the q-axis integral term component Vq_i, and the noninterference processing term component Vc,Ln for the q-axis to each other to calculate a q-axis command voltage Vq_c which is a command value for the voltage applied to the q-axis armature.
The motor control apparatus 1 also has a dq/3-phase converter 16 for converting the d-axis command volt-age Vd_c, the q-axis command voltage Vq_c, and the electri-cal angle 0 into three-phase command voltages VU_c, VV c, VW_c and outputting the three-phase command voltages VU_c, VV_c, vW c, a power drive unit 17 for being supplied with the three-phase command voltages VU c, VV c, VW c and out-putting frequency-variable voltages depending on the three-phase command voltages VU_c, VV_c, VW c to the armatures of the motor 2, and an angular velocity processor 19 for dif-ferentiating (d/dt) the detected signal of the electrical angle 0 from the position detecting sensor 5 to calculate an angular velocity co of the motor 2 and outputting the an-gular velocity c,u to the noninterference processor 18.
The first adder 14 and the second adder 15 jointly make up a command voltage generating means.
The integral term component generator 21 ap-proximates, with a steady gain M according to the equation (4), the steady input-to-output relationship of the motor 2 which is represented by a block 20 including the d-axis proportional term component generator 9 and the q-axis pro-portional term component generator 10, for being supplied with the voltage Vd applied to the d-axis armature and the voltage Vq applied to the q-axis armature and outputting the current Id flowing through the d-axis armature and the current iq flowing through the q-axis armature.
specifically, the integral term component gen-erator 21 approximates the input-to-output relationship with the steady gain M including the proportional gain xp as a parameter and also including the angular velocity w, the resistance r of the d-axis armature and the q-axis ar-mature, the inductance Ld of the d-axis armature, and the inductance Lp of the q-axis armature.
Then, the integral term component generator 21 effects an integrating process on the set of the d-axis current difference DId and the q-axis current difference AIq using, as an integral gain Ri, a gain for stabilizing the state of the output when the steady gain M, the d-axis current difference AId, and the q-axis current difference AIq are multiplied, integrated, and fed back.
Specifically, as indicated by the equation (11) shown below, the integral term component generator 21 mul-tiplies the set (AId, AIq)r of the d-axis current differ-ence AId and the q-axis current difference AIq by the inte-gral gain Ri, as indicated by 11 in FIG. 1, generates the d-axis integral term component Vd_i from the product ac-cording to the equation (7) as indicated by 12 in FIG. 1, and generates the q-axis integral term component Vq_i from the product according to the equation (8) as indicated by 13 in FIG. 1.
]K3. (DId ~ (k21 k22~dI
~ ~
11=AId+k12=AI = = = (11) ~21=t1Id+k22=AI
~
The d-axis integral term component Vd_i generat-ed by the integral term component generator 21 is added to the d-axis proportional term component Vd_p by the first adder 14, and the q-axis integral term component Vq_i gen-erated by the integral term component generator 21 is added to the q-axis proportional term component Vq_p by the sec-ond adder 15. The first and second adders.14, 15 input the d-axis command voltage Vd_c and the q-axis coinmand voltage Vq_c represented by the equation (12) shown below to the dq/3-phase converter 16.
r d c Kpdid + f'(k11 - AId +k12= bIq)dt - cvI,qlq.s +mIKc .
q _~ KpdIq + f(k21 = QId +k22 = DIq)dt -,;c:I.dId s ===(12) where w: the angular velocity of the motor 5, Ld: the in-ductance of the d-axis armature, Lq: the inductance of the q-axis armature, and Ke: the induced voltage constant.
The third term of the first line on the right side of the equation (12) represents the noninterference processing term component Vd n for the d-axis, whereas the third term of the second line on the right sicle of the equation (12) represents the noninterference processing term component Vq_n for the q-axis.
As described above, the integral term component generator 21 performs an integral process based on the in-tegral gain Ri which is determined to stabilize the output state when the steady gain N including the proportional gain Kp according to the equation (3) as a parameter, the d-axis current difference AId, and the q-axis current dif-ference DIq are multiplied, the product is irategrated, and the integrated product is fed back.
By generating the d-axis integral term component Vd_i which is an integral term component of the d-axis com-mand voltage Vd_c and the q-axis integral term component Vq_i which is an integral term component of the q-axis com-mand voltage Vq_c according to the above integral process, it is possible to bring the d-axis actual current Id s into stable conformity with the d-axis command current Id c and also bring the q-axis actual current Iq_s into stable con-formity with the q-axis command current Iq_c even if the proportional gain Kp is increased to increase the respon-siveness of the motor 2.
As a result, variations in the voltage Vd ap-plied to the d-axis armature and the voltage Vq applied to the q-axis armature and increases in the d-axis current difference AId and the q-axis current differeiace Aiq, both of which variations and increases are caused when the pro-portional gain is increased to operate the moitor at a high rotational speed in the conventional general PI control process, are suppressed, making it possible to control the motor with small variations in the voltages Vd, Vq and good responsiveness even when the motor 2 operates at high rota-tional speeds.
In the present embodiment, the integral term component generator 21 uses the integral gain Ki determined according to the equation (5). However, the product of a transposed matrix MT of the steady gain M determined by the equation (9) and a predetermined arbitrary positive defi-nite matrix Q may be used as the integral gain Ki.
The feedback control system shown in FIG. 2(a) may be considered in the form of the state feedback of the integrator as shown in FIG. 2(b), and the theory of an op-tim,um regulator may be applied to determine tlfie integral gain Ki. In this case, the state equation of an object to be controlled is expressed as the following equation (13):
dta-Ax+Bu (13) ...
y=cX
where A = 0, B = M, C- I.
Therefore, the Riccati's equation can be simpli-fied into the Liapunov's equation expressed by the equation (14) shown below, and the Liapunov's equation can be solved for its solution P to determine the integral grain Ki ac-cording to the equation (15) shown below.
-PMR''MrP + Q = 0 = = = (14 ) where Q, P, R: arbitrary positive definite matrixes.
Ki = -R-1MTP = = = (15) where R, P: arbitrary positive definite matrixes.
Furthermore, because the stability remains un-changed if the system shown in FIG. 2(b) is converted into a system shown FIG. 2(c), the integral gain Ki may be de-termined according to the following equation (16):
Ki = -M'' = M(M''R''MTP)M'1 ...
MR "'MTPM'~ ( ) = -detM = M'' {detM 1 M( where P, R: arbitrary positive definite matrixes.
Inasmuch as (-MR-IMTP) is stable due to the posi-tive definiteness of R, P, the above equation (16) has the term within the braces replaced with the stable matrix S
according to the equation (5). Alternatively,. the stable matrix S may be determined using the solution of the opti-mum regulator according to the equation (16).
Although certain preferred embodiments of the present invention have been shown and described in detail, it should be understood that various changes and modifica-tions may be made therein without departing from the scope of the appended claims.
Claims (4)
1. A motor control apparatus for converting a DC
brushless motor into an equivalent circuit having a q-axis armature on a q-axis which is aligned with the direction of magnetic fluxes of field systems of the motor and a d-axis armature on a d-axis which extends perpendicularly to the q-axis, comprising:
current detecting means for detecting currents flowing through armatures of the motor;
actual current calculating means for calculating a q-axis actual current flowing through said q-axis arma-ture and a d-axis actual current flowing through said d-axis armature from the currents detected by said current detecting means;
current difference calculating means for calcu-lating a q-axis current difference between a q-axis command current which is a command value for the current flowing through said q-axis armature and said q-axis actual current and a d-axis current difference between a d-axis command current which is a command value for the current flowing through said d-axis armature and said d-axis actual cur-rent;
means for generating a d-axis command voltage which is a command value for the voltage applied to said d-axis armature and a q-axis command voltage which is a com-mand value for the voltage applied to said q-axis armature in order to reduce said d-axis current difference and said q-axis current difference;
means for controlling the currents flowing through the armatures of the motor depending on said d-axis command voltage and said q-axis command voltage;
proportional term component generating means for carrying out a proportional process to multiply said d-axis current difference and said q-axis current difference by respective predetermined proportional gains to generate a d-axis proportional term component which is a proportional term component of said d-axis command voltage and a q-axis proportional term component which is a proportional term component of said q-axis command voltage;
integral term component generating means for ef-fecting an integrating process on said d-axis current dif-ference and said q-axis current difference based on a pre-determined integral gain to generate a d-axis integral term component which is an integral term component of said d-axis command voltage and a q-axis integral term component which is an integral term component of said q-axis command voltage; and command voltage generating means for generating said d-axis command voltage depending on the sum of said d-axis proportional term component and said d-axis integral term component, and said q-axis command voltage depending on the sum of said q-axis proportional term component and said q-axis integral term component;
means for setting said integral gain to stabi-lize a system in which said d-axis current difference and said q-axis current difference are multiplexed, integrated, and inputted, with respect to a steady gain which approxi-mates, including said proportional gains, the steady input-to-output relationship of said motor to which the voltage applied to said d-axis armature and the voltage applied to said q-axis armature are inputted and from which the cur-rent flowing through said d-axis armature and the current flowing through said q-axis armature are outputted.
brushless motor into an equivalent circuit having a q-axis armature on a q-axis which is aligned with the direction of magnetic fluxes of field systems of the motor and a d-axis armature on a d-axis which extends perpendicularly to the q-axis, comprising:
current detecting means for detecting currents flowing through armatures of the motor;
actual current calculating means for calculating a q-axis actual current flowing through said q-axis arma-ture and a d-axis actual current flowing through said d-axis armature from the currents detected by said current detecting means;
current difference calculating means for calcu-lating a q-axis current difference between a q-axis command current which is a command value for the current flowing through said q-axis armature and said q-axis actual current and a d-axis current difference between a d-axis command current which is a command value for the current flowing through said d-axis armature and said d-axis actual cur-rent;
means for generating a d-axis command voltage which is a command value for the voltage applied to said d-axis armature and a q-axis command voltage which is a com-mand value for the voltage applied to said q-axis armature in order to reduce said d-axis current difference and said q-axis current difference;
means for controlling the currents flowing through the armatures of the motor depending on said d-axis command voltage and said q-axis command voltage;
proportional term component generating means for carrying out a proportional process to multiply said d-axis current difference and said q-axis current difference by respective predetermined proportional gains to generate a d-axis proportional term component which is a proportional term component of said d-axis command voltage and a q-axis proportional term component which is a proportional term component of said q-axis command voltage;
integral term component generating means for ef-fecting an integrating process on said d-axis current dif-ference and said q-axis current difference based on a pre-determined integral gain to generate a d-axis integral term component which is an integral term component of said d-axis command voltage and a q-axis integral term component which is an integral term component of said q-axis command voltage; and command voltage generating means for generating said d-axis command voltage depending on the sum of said d-axis proportional term component and said d-axis integral term component, and said q-axis command voltage depending on the sum of said q-axis proportional term component and said q-axis integral term component;
means for setting said integral gain to stabi-lize a system in which said d-axis current difference and said q-axis current difference are multiplexed, integrated, and inputted, with respect to a steady gain which approxi-mates, including said proportional gains, the steady input-to-output relationship of said motor to which the voltage applied to said d-axis armature and the voltage applied to said q-axis armature are inputted and from which the cur-rent flowing through said d-axis armature and the current flowing through said q-axis armature are outputted.
2. A motor control apparatus according to claim 1, wherein said steady gain is expressed by the following equation (17), and said input-to-output relationship is ex-pressed by the following equation (18):
where M: said steady gain, r: the resistance of said d-axis armature and said q-axis armature, Kp: said proportional gains, Ld: the inductance of said d-axis armature, and Lq:
the inductance of said q-axis armature;
where Id: the current flowing through said d-axis armature, Iq: the current flowing through said q-axis armature, .omega.:
the angular velocity of said motor, Vd: the voltage applied to said d-axis armature, and Vq: the voltage applied to said q-axis armature.
where M: said steady gain, r: the resistance of said d-axis armature and said q-axis armature, Kp: said proportional gains, Ld: the inductance of said d-axis armature, and Lq:
the inductance of said q-axis armature;
where Id: the current flowing through said d-axis armature, Iq: the current flowing through said q-axis armature, .omega.:
the angular velocity of said motor, Vd: the voltage applied to said d-axis armature, and Vq: the voltage applied to said q-axis armature.
3. A motor control apparatus according to claim 2, wherein said integral gain is determined by the follow-ing equation (19), and said integrating process is carried out according to the following equations (20) and (21):
where Ki: said integral gain, detM: the matrix equation of the steady gain M according to said equation (17), and S: a predetermined arbitrary stable matrix;
where Vd_i: said d-axis integral term component, Vq_i: said q-axis integral term component, .DELTA.Id: said d-axis current difference, .DELTA.Iq: said q-axis current difference, k11, k12, k21, k22: matrix elements of the integral gain Ki defined by said equation (19).
where Ki: said integral gain, detM: the matrix equation of the steady gain M according to said equation (17), and S: a predetermined arbitrary stable matrix;
where Vd_i: said d-axis integral term component, Vq_i: said q-axis integral term component, .DELTA.Id: said d-axis current difference, .DELTA.Iq: said q-axis current difference, k11, k12, k21, k22: matrix elements of the integral gain Ki defined by said equation (19).
4. A motor control apparatus according to claim 2, wherein said integral gain is determined by the follow-ing equation (22), and said integrating process is carried out according to the following equations (23) and (24):
where Ki: said integral gain, M: the steady gain according to said equation (17), M T: a transposed matrix of M, and Q:
a predetermined arbitrary positive definite matrix;
where Vd_i: said d-axis integral term component, Vq_i: said q-axis integral term component, .DELTA.Id: said d-axis current difference, .DELTA.Iq: said q-axis current difference, k11, k12, k21, k22: matrix elements of the integral gain Ki defined by said equation (22).
where Ki: said integral gain, M: the steady gain according to said equation (17), M T: a transposed matrix of M, and Q:
a predetermined arbitrary positive definite matrix;
where Vd_i: said d-axis integral term component, Vq_i: said q-axis integral term component, .DELTA.Id: said d-axis current difference, .DELTA.Iq: said q-axis current difference, k11, k12, k21, k22: matrix elements of the integral gain Ki defined by said equation (22).
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001040445A JP3527207B2 (en) | 2001-02-16 | 2001-02-16 | Motor control device |
| JP2001-40445 | 2001-02-16 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CA2372134A1 CA2372134A1 (en) | 2002-08-16 |
| CA2372134C true CA2372134C (en) | 2009-05-26 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA002372134A Expired - Fee Related CA2372134C (en) | 2001-02-16 | 2002-02-13 | Motor control apparatus |
Country Status (4)
| Country | Link |
|---|---|
| US (1) | US6608456B2 (en) |
| JP (1) | JP3527207B2 (en) |
| CA (1) | CA2372134C (en) |
| DE (1) | DE10206156B4 (en) |
Families Citing this family (13)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP4665360B2 (en) * | 2001-08-06 | 2011-04-06 | 株式会社安川電機 | Electric motor control device |
| JP3644922B2 (en) * | 2001-12-06 | 2005-05-11 | 本田技研工業株式会社 | Electric power steering device |
| JP3812739B2 (en) * | 2002-05-28 | 2006-08-23 | 三菱電機株式会社 | Motor abnormality detection device and electric power steering control device |
| JP3914107B2 (en) * | 2002-07-12 | 2007-05-16 | 本田技研工業株式会社 | DC brushless motor control device |
| JP3914108B2 (en) * | 2002-07-15 | 2007-05-16 | 本田技研工業株式会社 | DC brushless motor control device |
| US20060043923A1 (en) * | 2004-08-31 | 2006-03-02 | Baker Donal E | Performance enhancement for motor field oriented control system |
| JP4764785B2 (en) * | 2006-08-23 | 2011-09-07 | ルネサスエレクトロニクス株式会社 | Control device for synchronous motor |
| KR101382749B1 (en) * | 2012-04-13 | 2014-04-08 | 현대자동차주식회사 | Method for correcting resolver offset |
| US9035587B2 (en) * | 2013-03-14 | 2015-05-19 | Cirrus Logic Inc. | Motor control loop with fast response |
| DE102013221957A1 (en) * | 2013-10-29 | 2015-04-30 | Continental Teves Ag & Co. Ohg | Method and device for operating a permanent-magnet synchronous machine |
| DE102013222075A1 (en) * | 2013-10-30 | 2015-03-05 | Zf Friedrichshafen Ag | Apparatus and method for initializing a control circuit for a current for operating a synchronous machine |
| CN109305050B (en) * | 2018-09-28 | 2022-06-24 | 上汽通用五菱汽车股份有限公司 | Control method, motor controller, electric vehicle, and computer-readable storage medium |
| CN112332734B (en) * | 2020-09-07 | 2021-11-23 | 江苏大学 | Ultrahigh-speed electric air compressor variable voltage stability expansion control system and method for improving large-range speed regulation response capability |
Family Cites Families (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4808903A (en) * | 1987-04-13 | 1989-02-28 | Hitachi, Ltd. | Vector control system for induction motors |
| US4958117A (en) * | 1989-09-29 | 1990-09-18 | Allen-Bradley Company, Inc. | Frequency control based on sensing voltage fed to an induction motor |
| JPH05260781A (en) * | 1992-03-09 | 1993-10-08 | Mitsubishi Electric Corp | Power conversion apparatus |
| US5329217A (en) * | 1992-12-30 | 1994-07-12 | Allen-Bradley Company, Inc. | Compensated feedforward voltage for a PWM AC motor drive |
| JPH08182398A (en) * | 1994-12-27 | 1996-07-12 | Fuji Electric Co Ltd | Driving device for permanent magnet-type synchronous motor |
| JP3321356B2 (en) * | 1996-05-20 | 2002-09-03 | 株式会社日立製作所 | Motor control device and control device for electric vehicle |
| US6018225A (en) * | 1998-02-09 | 2000-01-25 | Allen-Bradley Company, Llc | Method and apparatus for reconnecting a rotating motor to a motor drive |
| US6407531B1 (en) * | 2001-01-09 | 2002-06-18 | Delphi Technologies, Inc. | Method and system for controlling a synchronous machine over full operating range |
-
2001
- 2001-02-16 JP JP2001040445A patent/JP3527207B2/en not_active Expired - Fee Related
-
2002
- 2002-02-13 CA CA002372134A patent/CA2372134C/en not_active Expired - Fee Related
- 2002-02-14 DE DE10206156A patent/DE10206156B4/en not_active Expired - Fee Related
- 2002-02-14 US US10/073,905 patent/US6608456B2/en not_active Expired - Fee Related
Also Published As
| Publication number | Publication date |
|---|---|
| JP3527207B2 (en) | 2004-05-17 |
| CA2372134A1 (en) | 2002-08-16 |
| DE10206156A1 (en) | 2002-10-10 |
| JP2002247877A (en) | 2002-08-30 |
| US6608456B2 (en) | 2003-08-19 |
| US20020149330A1 (en) | 2002-10-17 |
| DE10206156B4 (en) | 2008-02-07 |
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