CA1232988A - Subscriber line interface circuit with improved d.c. balance - Google Patents
Subscriber line interface circuit with improved d.c. balanceInfo
- Publication number
- CA1232988A CA1232988A CA000490968A CA490968A CA1232988A CA 1232988 A CA1232988 A CA 1232988A CA 000490968 A CA000490968 A CA 000490968A CA 490968 A CA490968 A CA 490968A CA 1232988 A CA1232988 A CA 1232988A
- Authority
- CA
- Canada
- Prior art keywords
- coupled
- output
- current
- slic
- terminals
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04M—TELEPHONIC COMMUNICATION
- H04M19/00—Current supply arrangements for telephone systems
- H04M19/001—Current supply source at the exchanger providing current to substations
- H04M19/005—Feeding arrangements without the use of line transformers
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04M—TELEPHONIC COMMUNICATION
- H04M3/00—Automatic or semi-automatic exchanges
- H04M3/005—Interface circuits for subscriber lines
Landscapes
- Engineering & Computer Science (AREA)
- Signal Processing (AREA)
- Power Engineering (AREA)
- Interface Circuits In Exchanges (AREA)
Abstract
SUBSCRIBER LINE INTERFACE CIRCUIT WITH
IMPROVED D.C. BALANCE
Abstract of the Disclosure A SLIC includes controlled current circuits (CCCs) which simulate feed resistors for controlling d.c. feed to a two-wire telephone subscriber line which is coupled to two terminals, control being achieved via a feedback loop. A differential amplifier has an inverting input coupled to the tapping point of a potential divider connected between the terminals, and a non-inverting input connected to a reference potential of half of the supply battery voltage. For suppressing longitudinal currents on the line, the amplifier output is connected to each terminal via a d.c. blocking capacitor in series with a resistor, the resistors having closely matched resistances.
For maintaining d.c. balance, the output of the amplifier is coupled via a low pass filter to control a current splitter included in the feedback loop, to control the relative proportions of control currents for the CCCs.
-i-
IMPROVED D.C. BALANCE
Abstract of the Disclosure A SLIC includes controlled current circuits (CCCs) which simulate feed resistors for controlling d.c. feed to a two-wire telephone subscriber line which is coupled to two terminals, control being achieved via a feedback loop. A differential amplifier has an inverting input coupled to the tapping point of a potential divider connected between the terminals, and a non-inverting input connected to a reference potential of half of the supply battery voltage. For suppressing longitudinal currents on the line, the amplifier output is connected to each terminal via a d.c. blocking capacitor in series with a resistor, the resistors having closely matched resistances.
For maintaining d.c. balance, the output of the amplifier is coupled via a low pass filter to control a current splitter included in the feedback loop, to control the relative proportions of control currents for the CCCs.
-i-
Description
S~BSCRIBE~ LINE INTERFACE CIRCUIT W[TH IMPROVED D.C. ~ALANCE
. .
This invention relates to subscriber line interface circuits (SLICs), which provide for coupling to two-wire telephone subscriber lines.
Reference is directed to my copending pa-tent application entitled "Subscriber Lirle Inter-Face Circuit with Longitudinal Current Suppression" an~l filed simultaneously herewith, the claims of which are directed to a SLIC including features an embodiment of which is also described herein.
Many proposals exist for providing a SLIC in the form o-f an integrated circuit and -for coupliny this to a two-wire telephone subscriber line, preferably using direct coupling, i.e. without an intervening transformer. One such proposal, in which the SLIC
comprises controlled current circuits (also referred to as current mirror circuits~ current sources, and current sinks), is described in Kelley et al. U.S. Patent No. 4,300,023 issued November 10, l9Sl, and entitled "Hybrid Circuit". In this known SLIC, controlled current circuits are coupled to the tip and ring wires of the telephone subscriber line and are controlled to provide a desired d.c. -feed resistance.
It is also well known that d.c. balance of two-wire telephone subscriber lines must be closely maintained. In the SLIC described in the above patent, it is assumed that d.c. balance will be achieved by virtue of the fact that the controlled current circuits, which serve to simulate d.c. feed resistors, are coupled to the tip and ring wires using a generally symmetrical or balanced arrangement and are formed in the same integrated circuitO This assumption fails in practice, however, because matching of the controlled current circuits to better than about 1% is difficult or impossible to achieve.
Accordingly, an object of this invention is to provide an improved SLIC which enables d.c. balance of a two-wire line, which is coupled to the SLIC in opera-tion, to be enhanced.
According to this invention -there is provided a subscriber line interface circuit (SLIC) comprising: two terminals for coupling to a two-wire telephone subscriber line; two controlled current circuits (CCCs) for respectively supplying direct current to and "~
sinking direct curren-t from the line via the terminals; a feedback loop responsive to direct current on the line for controlling the CCCs; and d.c. balance control means responsive to a d.c. imbalance of potentials at the terminals for controlling the feedback loop to modify control of the CCCs to reduce the d.c. imbalance~ the d.c.
balance control means comprising a poten-tial divider coupled between the terMinals and having d tapping point; and a differential amplifier having a first input coupled to the tapping point, a second input coupled to a point of reference potential, and an output coupled to an ou-tput of the d.c. balance control means.
Thus in a SLIC in accordance with this invention the feedback control of the CCCs which serve to simulate doc~ feed resistors is modified to maintain d.c. balance.
In an embodiment of the invention the feedback loop comprises means for producing a sum current dependent upon a sum of direct currents flowing via the terminals; current splitting means for splitting the sum current into two control currents; and means for controlling the two CCCs each in dependence upon a respective one of the two control currents; wherein the current splitting means is responsive to the output of the d.c. balance control means to control the relative proportions of the two control currents.
Conveniently the current splitting means comprises two transistors having bases coupled respectively to the output of the d.c. balance control means and to a point of reference potential, and having emitters coupled together and supplied with the sum current, and means for deriving the two control currents from collectors of the transistors.
The d.c. balance control means preferably further comprises low pass filter means coupled between the output of the differential amplifier and the output of the d.c. balance control means.
This arrangement also enables longitudinal currents, which are common mode alternating currents typically induced on the two-wire telephone subscriber line from adjacent power lines and/or as a result of cross-talk from other telephone lines, to be suppressed in a particularly convenient manner. To this end preferably the first input of the differential amplifier is an inverting input, and the SLIC further comprises a resistor and a ~2~ 3 capacitor coupled in series between each o-f -the terminals and -the output of the di-Fferential amplifier.
The invention will be -further understood from the following description with re~erence to -the accompanying drawings, in which:
Fig. 1 schema-tically illustrdtes parts of a subscriber line interface circuit (SLIC) in accordance with this inven-tion; and Figs. 2 to 7 schelnatically illus-trate the particular forms of controlled current circuits (CCCs) used in the SLIC o-f Fig. 1.
Referring to Fig. 1, only those parts of a SLIC which are relevant to this invention are shown, other parts, for example -for handling voice frequency signals and for applying ringing signals to a telephone subscriber line 10 to which the SLIC is connected, are not shown but are provided in known rnanner, for example in the manner described in Kelley et al. U.S. Patent No. 4,300,023 already referred to.
The parts of the SLIC which are illustrated in Fig. 1 include six CCCs (controlled current circuits) 2 to 7 each of which is represented in Fig. 1 by a circle having three connections. Each CCC
has a controlled current path, for which the direction of current is shown in Fig. 1 by an arrow within the respective circuit and aligned wi-th the connections to this path, and a controlling current path for which the direction of current is shown on a side connection to the respective circle. Thus each CCC is a current mirror circuit in which the current in the controlled path is directly proportional to the current in the controlling path, with a propor-tionality factor which is referred to as being the gain of the circuit.
Such CCCs are generally known and can take various forms.
For the sake of completeness of this description, Figs. 2 to 7 illustrate particular forms which the CCCs 2 to 7 respectively may have in one particular embodiment of the invention, it being understood that other forms of these circuits may be adopted. The positions and orientations of Figs. 2 to 7 correspond to those of the respective CCCs 2 to 7 in Fig. 1.
As illustra-ted in Figs. 2 to 7, each CCC comprises three NPN
or PNP (depending on the desired current direction) transistors, two of which have their bases interconnected and have their emitters interconnected Vid respective emitter resistors, resistance values :~3~
for which are given in nhrns in Figs. 2 to 7. The ra-tio of the resistances of the emitter resistors in each CCC, which is made the same dS the ernitter ared ra-tio of the transistors, determines the gain of the CCC. The -third transistor of each CCC has its base connected to the controlling current pa-th and its emi-tter connected to the bases of the other two transistors.
In addition to the CCCs 2 to 7, as illustrated in Fig. 1 the SLIC also includes a differential amplifier 12, a further differential ampli-Fier constituted by two transistors 14 and 16, resistors 18 to 28, and capacitors 30 to 32. The components 2 to 7, 12, 14, 16, and 24 to 28 are conveniently formed in an integrated circuit together with other parts of the SLIC which are not shown.
The SLIC is supplied with power from d negative supply voltage VB, which is nominally ~48 volts and is typically derived from a telephone central office battery, and a positive supply voltage of +15 volts, both with respect to ground or 0 volts.
The CCCs 3 and 6 serve to supply (d.c.~ loop current I to terminals -r and R of the integrated circuit, and thence to the tip and ring wires of the subscriber line 10 via resistors 18 and 19, which have closely matched resistances of for example 200 ohms each.
As described in Jakab U.S. Patent No. 4,467,310 issued August 21, 1984, these resistors can comprise thick film resistors connected in series with switching type PTC resistors, all mounted on a common substrate for thermal coupling. The loop current is controlled in dependence upon the resistances of, and is partly also supplied via, the resistors 20 and 21; for example these resistors have matched resistances of 22 kilohms each. The resistors 20 to 23 are also conveniently thick film resistors.
The ,oart of the loop current which flows via the resistor 20 is mirrored by the CCC 2, and the resultant current is summed at a junction point 34 with the part of the loop current which flows via the resistor 21 to produce d control current for the CCC 7. The controlled path current of the CCC 7, which flows via the emitters of the transistors 14 and 16 and their common emitter resistor 28, is initidlly assumed to be equally shared between these two transistors to provide equal control currents for the CCCs 4 and 5. The controlled currents produced by these CCCs in turn produce equal control currents for the CCCs 3 and 6.
From the above description, it should be appreciated tha-t the CCCs 3 and 6 serve to simulate feed resis-tors for supplying the loop current I to the subscriber line lO. For the same reasons that such feed resistors must be c-losely matched to provide a d.c. balanced arrangement (For example, this is needed For some automatic number identification detectors), so the CCCs 3 and 6 should be closely matclled for cl.c. balance purposes. Ilowever, perfect matching o-f these CCCs in the SLIC integrated circuit is not possible, resulting in some degree o-f d.c. imbalance. In the SLIC as illustrated in Fig.
1, d.c. imbalance is corrected in the manner described below.
The resistors 24 and 25 form a potential divider between the terminals T and R, and have resistances of 100 kilohms each which are matched to 0.1% to 2% depending on the integra-ted circuit process which is used. In a state of d.c. balance, the d.c. potential at the junction be-tween these resistors is equal to half the supply voltage VB. The differential amplifier 12 has its inverting input connected to this junction and its non-inverting input supplied (for example from a potential divider which is not illustrated) with the voltage VB/2. Consequently, any d.c. imbalance results in the amplifier 12 producing an output signal with a d.c. component which differs from VB/2, the difference consti-tuting an amplified error signal.
The output of the amplifier 12 is connected via a low-pass filter, constituted by the resistors 26 and 27 and the capacitor 32, to the base of the transistor 14. The resistors 26 and 27 each have a resistance of 100 kilohms, and the capacitor 32 has a capacitance of 330nF, so that the low-pass filter has a cut-off frequency well below voice-band and power line frequencies. Consequently only the d.c. component of the signal at the output of the amplifier 12 is applied to the base of the transistor 14. The voltage VB/2 is applied to the base of the transistor 16, so that the differential amplifier formed by these two transistors is supplied with a differential input signal constituted by the amplified error signal, which thereby controls the sharing of the controlled curren-t from the CCC 7 between the transistors 14 and 16. In consequence, the CCCs 3 and 6 are controlled to correct the d.c. imbalance.
For example, iF the e-F~ective impedance of the CCC 3 is less than tha-t of the CCC 6, then a d.c. imbalance tends to arise causing -the signal at the inver-ting input of -the amplifier 12 to have a d.c.
component more positive than V3/2~ In consequence, the d.c.
component o-F the s-ignal at the output of the amplifier 12 is more negative than VB/2, and the transistor 14 conducts less than half, and the transistor 16 conducts more than hdlf, o-F the total (constant) curren-t passed by -the CCC 7. Consequently the CCCs ~ and 3 pass less current, with a corresponding increase in ef-fective impedance, and the CCCs 5 and 6 pass more current, with a corresponding decrease in effective impedance, thereby substantia11y correcting the d.c. imbalanceO
In addition to serving in maintaining d.c. balance in the manner described above, -the resistors 24 and 25 and the amplifier 12 also serve wi-th the resistors 22 and 23 and the capacitors 30 and 31 to compensate for longitudinal currents on the subscriber line 10. Longitudinal currents may for example arise as a result of induction from power lines and/or crosstalk from other subscriber lines, and comprise alternating currents, represented as i in Fig. 1, which flow in the same direction on both of the tip and ring wires of the subscriber line 10.
It is known to compensate for longitudinal currents by providing two commonly controlled current sinks which would be coupled to the terminals T and R. For longitudinal current balance it is necessary for such current sinks to be closely matched, for example within about 0.1~, and this is very difficul-t or impossible to achieve if the current sinks are formed in an integrated circuit for which matching is not normally better than 1%. This problem is avoided by the circuit illustrated in Fig. 1.
As illustrated in Fig. 1, the terminal T is coupled via the resistor 22 and the capacitor 30 to a junction point 36, and the terminal R is similarly coupled to this point 36 via the resistor 23 and the capacitor 31. The resistors 22 and 23 are for example thick film resistors each having a resistance of 500 ohms, the resistances 35 being closely matched to within 0.1X. The capacitors 30 and 31 serve to block d.c. so that d.c. line curren-ts are not affected by the presence of the resis-tors 22 and 23, and for example have capaci-tances of 33 microfarads and a tolerance oF 5%. The junction point 36 is connected to the outpu-t of the differential amplifier 12, which acts as a controlled voltage source for longi-tudinal currents.
Thus in the SLIC illustrated in Fig. 1, -the controlled current sinks of the prior art are replaced by the closely matched resistors 22 and 23 toyether wi-th a controlled voltage source.
If~ for exanlple, the (a.c.) longi-tudinal current i increases, tending to make the po-tentials at the terminals T and R more positive, -then via the resis-tors 24 and 25 the potential at the inverting input of the amplifier also tends to become rnore positive.
The fixed potential V~/2 at the non-inverting input of the amplifier 12 constitutes an a.c~ ground. In consequence, the potential at the output of the ampli-fier 12, and hence at the junction point 36, tends to become more negative, increasing the (a.c.) potential difference across the resistors 22 and 23 and thereby passing more current to compensate for the increased longitudinal current i. In consequence, the terminals T and R are virtual ground points for longitudinal al-ternating currents. The potentials at these terminals can change differentially, however, without affecting the potential at the inverting input of the amplifier 12, so that -the desired transmission of differential voice frequency signals on the subscriber line 10 is not adversely affected.
It should be appreciated that numerous modi-fications, variations, and adaptations may be made to the particular embodiment of the invention described above without departing from the scope of the invention as defined in the claims.
. .
This invention relates to subscriber line interface circuits (SLICs), which provide for coupling to two-wire telephone subscriber lines.
Reference is directed to my copending pa-tent application entitled "Subscriber Lirle Inter-Face Circuit with Longitudinal Current Suppression" an~l filed simultaneously herewith, the claims of which are directed to a SLIC including features an embodiment of which is also described herein.
Many proposals exist for providing a SLIC in the form o-f an integrated circuit and -for coupliny this to a two-wire telephone subscriber line, preferably using direct coupling, i.e. without an intervening transformer. One such proposal, in which the SLIC
comprises controlled current circuits (also referred to as current mirror circuits~ current sources, and current sinks), is described in Kelley et al. U.S. Patent No. 4,300,023 issued November 10, l9Sl, and entitled "Hybrid Circuit". In this known SLIC, controlled current circuits are coupled to the tip and ring wires of the telephone subscriber line and are controlled to provide a desired d.c. -feed resistance.
It is also well known that d.c. balance of two-wire telephone subscriber lines must be closely maintained. In the SLIC described in the above patent, it is assumed that d.c. balance will be achieved by virtue of the fact that the controlled current circuits, which serve to simulate d.c. feed resistors, are coupled to the tip and ring wires using a generally symmetrical or balanced arrangement and are formed in the same integrated circuitO This assumption fails in practice, however, because matching of the controlled current circuits to better than about 1% is difficult or impossible to achieve.
Accordingly, an object of this invention is to provide an improved SLIC which enables d.c. balance of a two-wire line, which is coupled to the SLIC in opera-tion, to be enhanced.
According to this invention -there is provided a subscriber line interface circuit (SLIC) comprising: two terminals for coupling to a two-wire telephone subscriber line; two controlled current circuits (CCCs) for respectively supplying direct current to and "~
sinking direct curren-t from the line via the terminals; a feedback loop responsive to direct current on the line for controlling the CCCs; and d.c. balance control means responsive to a d.c. imbalance of potentials at the terminals for controlling the feedback loop to modify control of the CCCs to reduce the d.c. imbalance~ the d.c.
balance control means comprising a poten-tial divider coupled between the terMinals and having d tapping point; and a differential amplifier having a first input coupled to the tapping point, a second input coupled to a point of reference potential, and an output coupled to an ou-tput of the d.c. balance control means.
Thus in a SLIC in accordance with this invention the feedback control of the CCCs which serve to simulate doc~ feed resistors is modified to maintain d.c. balance.
In an embodiment of the invention the feedback loop comprises means for producing a sum current dependent upon a sum of direct currents flowing via the terminals; current splitting means for splitting the sum current into two control currents; and means for controlling the two CCCs each in dependence upon a respective one of the two control currents; wherein the current splitting means is responsive to the output of the d.c. balance control means to control the relative proportions of the two control currents.
Conveniently the current splitting means comprises two transistors having bases coupled respectively to the output of the d.c. balance control means and to a point of reference potential, and having emitters coupled together and supplied with the sum current, and means for deriving the two control currents from collectors of the transistors.
The d.c. balance control means preferably further comprises low pass filter means coupled between the output of the differential amplifier and the output of the d.c. balance control means.
This arrangement also enables longitudinal currents, which are common mode alternating currents typically induced on the two-wire telephone subscriber line from adjacent power lines and/or as a result of cross-talk from other telephone lines, to be suppressed in a particularly convenient manner. To this end preferably the first input of the differential amplifier is an inverting input, and the SLIC further comprises a resistor and a ~2~ 3 capacitor coupled in series between each o-f -the terminals and -the output of the di-Fferential amplifier.
The invention will be -further understood from the following description with re~erence to -the accompanying drawings, in which:
Fig. 1 schema-tically illustrdtes parts of a subscriber line interface circuit (SLIC) in accordance with this inven-tion; and Figs. 2 to 7 schelnatically illus-trate the particular forms of controlled current circuits (CCCs) used in the SLIC o-f Fig. 1.
Referring to Fig. 1, only those parts of a SLIC which are relevant to this invention are shown, other parts, for example -for handling voice frequency signals and for applying ringing signals to a telephone subscriber line 10 to which the SLIC is connected, are not shown but are provided in known rnanner, for example in the manner described in Kelley et al. U.S. Patent No. 4,300,023 already referred to.
The parts of the SLIC which are illustrated in Fig. 1 include six CCCs (controlled current circuits) 2 to 7 each of which is represented in Fig. 1 by a circle having three connections. Each CCC
has a controlled current path, for which the direction of current is shown in Fig. 1 by an arrow within the respective circuit and aligned wi-th the connections to this path, and a controlling current path for which the direction of current is shown on a side connection to the respective circle. Thus each CCC is a current mirror circuit in which the current in the controlled path is directly proportional to the current in the controlling path, with a propor-tionality factor which is referred to as being the gain of the circuit.
Such CCCs are generally known and can take various forms.
For the sake of completeness of this description, Figs. 2 to 7 illustrate particular forms which the CCCs 2 to 7 respectively may have in one particular embodiment of the invention, it being understood that other forms of these circuits may be adopted. The positions and orientations of Figs. 2 to 7 correspond to those of the respective CCCs 2 to 7 in Fig. 1.
As illustra-ted in Figs. 2 to 7, each CCC comprises three NPN
or PNP (depending on the desired current direction) transistors, two of which have their bases interconnected and have their emitters interconnected Vid respective emitter resistors, resistance values :~3~
for which are given in nhrns in Figs. 2 to 7. The ra-tio of the resistances of the emitter resistors in each CCC, which is made the same dS the ernitter ared ra-tio of the transistors, determines the gain of the CCC. The -third transistor of each CCC has its base connected to the controlling current pa-th and its emi-tter connected to the bases of the other two transistors.
In addition to the CCCs 2 to 7, as illustrated in Fig. 1 the SLIC also includes a differential amplifier 12, a further differential ampli-Fier constituted by two transistors 14 and 16, resistors 18 to 28, and capacitors 30 to 32. The components 2 to 7, 12, 14, 16, and 24 to 28 are conveniently formed in an integrated circuit together with other parts of the SLIC which are not shown.
The SLIC is supplied with power from d negative supply voltage VB, which is nominally ~48 volts and is typically derived from a telephone central office battery, and a positive supply voltage of +15 volts, both with respect to ground or 0 volts.
The CCCs 3 and 6 serve to supply (d.c.~ loop current I to terminals -r and R of the integrated circuit, and thence to the tip and ring wires of the subscriber line 10 via resistors 18 and 19, which have closely matched resistances of for example 200 ohms each.
As described in Jakab U.S. Patent No. 4,467,310 issued August 21, 1984, these resistors can comprise thick film resistors connected in series with switching type PTC resistors, all mounted on a common substrate for thermal coupling. The loop current is controlled in dependence upon the resistances of, and is partly also supplied via, the resistors 20 and 21; for example these resistors have matched resistances of 22 kilohms each. The resistors 20 to 23 are also conveniently thick film resistors.
The ,oart of the loop current which flows via the resistor 20 is mirrored by the CCC 2, and the resultant current is summed at a junction point 34 with the part of the loop current which flows via the resistor 21 to produce d control current for the CCC 7. The controlled path current of the CCC 7, which flows via the emitters of the transistors 14 and 16 and their common emitter resistor 28, is initidlly assumed to be equally shared between these two transistors to provide equal control currents for the CCCs 4 and 5. The controlled currents produced by these CCCs in turn produce equal control currents for the CCCs 3 and 6.
From the above description, it should be appreciated tha-t the CCCs 3 and 6 serve to simulate feed resis-tors for supplying the loop current I to the subscriber line lO. For the same reasons that such feed resistors must be c-losely matched to provide a d.c. balanced arrangement (For example, this is needed For some automatic number identification detectors), so the CCCs 3 and 6 should be closely matclled for cl.c. balance purposes. Ilowever, perfect matching o-f these CCCs in the SLIC integrated circuit is not possible, resulting in some degree o-f d.c. imbalance. In the SLIC as illustrated in Fig.
1, d.c. imbalance is corrected in the manner described below.
The resistors 24 and 25 form a potential divider between the terminals T and R, and have resistances of 100 kilohms each which are matched to 0.1% to 2% depending on the integra-ted circuit process which is used. In a state of d.c. balance, the d.c. potential at the junction be-tween these resistors is equal to half the supply voltage VB. The differential amplifier 12 has its inverting input connected to this junction and its non-inverting input supplied (for example from a potential divider which is not illustrated) with the voltage VB/2. Consequently, any d.c. imbalance results in the amplifier 12 producing an output signal with a d.c. component which differs from VB/2, the difference consti-tuting an amplified error signal.
The output of the amplifier 12 is connected via a low-pass filter, constituted by the resistors 26 and 27 and the capacitor 32, to the base of the transistor 14. The resistors 26 and 27 each have a resistance of 100 kilohms, and the capacitor 32 has a capacitance of 330nF, so that the low-pass filter has a cut-off frequency well below voice-band and power line frequencies. Consequently only the d.c. component of the signal at the output of the amplifier 12 is applied to the base of the transistor 14. The voltage VB/2 is applied to the base of the transistor 16, so that the differential amplifier formed by these two transistors is supplied with a differential input signal constituted by the amplified error signal, which thereby controls the sharing of the controlled curren-t from the CCC 7 between the transistors 14 and 16. In consequence, the CCCs 3 and 6 are controlled to correct the d.c. imbalance.
For example, iF the e-F~ective impedance of the CCC 3 is less than tha-t of the CCC 6, then a d.c. imbalance tends to arise causing -the signal at the inver-ting input of -the amplifier 12 to have a d.c.
component more positive than V3/2~ In consequence, the d.c.
component o-F the s-ignal at the output of the amplifier 12 is more negative than VB/2, and the transistor 14 conducts less than half, and the transistor 16 conducts more than hdlf, o-F the total (constant) curren-t passed by -the CCC 7. Consequently the CCCs ~ and 3 pass less current, with a corresponding increase in ef-fective impedance, and the CCCs 5 and 6 pass more current, with a corresponding decrease in effective impedance, thereby substantia11y correcting the d.c. imbalanceO
In addition to serving in maintaining d.c. balance in the manner described above, -the resistors 24 and 25 and the amplifier 12 also serve wi-th the resistors 22 and 23 and the capacitors 30 and 31 to compensate for longitudinal currents on the subscriber line 10. Longitudinal currents may for example arise as a result of induction from power lines and/or crosstalk from other subscriber lines, and comprise alternating currents, represented as i in Fig. 1, which flow in the same direction on both of the tip and ring wires of the subscriber line 10.
It is known to compensate for longitudinal currents by providing two commonly controlled current sinks which would be coupled to the terminals T and R. For longitudinal current balance it is necessary for such current sinks to be closely matched, for example within about 0.1~, and this is very difficul-t or impossible to achieve if the current sinks are formed in an integrated circuit for which matching is not normally better than 1%. This problem is avoided by the circuit illustrated in Fig. 1.
As illustrated in Fig. 1, the terminal T is coupled via the resistor 22 and the capacitor 30 to a junction point 36, and the terminal R is similarly coupled to this point 36 via the resistor 23 and the capacitor 31. The resistors 22 and 23 are for example thick film resistors each having a resistance of 500 ohms, the resistances 35 being closely matched to within 0.1X. The capacitors 30 and 31 serve to block d.c. so that d.c. line curren-ts are not affected by the presence of the resis-tors 22 and 23, and for example have capaci-tances of 33 microfarads and a tolerance oF 5%. The junction point 36 is connected to the outpu-t of the differential amplifier 12, which acts as a controlled voltage source for longi-tudinal currents.
Thus in the SLIC illustrated in Fig. 1, -the controlled current sinks of the prior art are replaced by the closely matched resistors 22 and 23 toyether wi-th a controlled voltage source.
If~ for exanlple, the (a.c.) longi-tudinal current i increases, tending to make the po-tentials at the terminals T and R more positive, -then via the resis-tors 24 and 25 the potential at the inverting input of the amplifier also tends to become rnore positive.
The fixed potential V~/2 at the non-inverting input of the amplifier 12 constitutes an a.c~ ground. In consequence, the potential at the output of the ampli-fier 12, and hence at the junction point 36, tends to become more negative, increasing the (a.c.) potential difference across the resistors 22 and 23 and thereby passing more current to compensate for the increased longitudinal current i. In consequence, the terminals T and R are virtual ground points for longitudinal al-ternating currents. The potentials at these terminals can change differentially, however, without affecting the potential at the inverting input of the amplifier 12, so that -the desired transmission of differential voice frequency signals on the subscriber line 10 is not adversely affected.
It should be appreciated that numerous modi-fications, variations, and adaptations may be made to the particular embodiment of the invention described above without departing from the scope of the invention as defined in the claims.
Claims (6)
1. A subscriber line interface circuit (SLIC) comprising:
two terminals for coupling to a two-wire telephone subscriber line;
two controlled current circuits (CCCs) for respectively supplying direct current to and sinking direct current from the line via the terminals;
a feedback loop responsive to direct current on the line for controlling the CCCs; and d.c. balance control means responsive to a d.c. imbalance of potentials at the terminals for controlling the feedback loop to modify control of the CCCs to reduce the d.c. imbalance;
the d.c. balance control means comprising:
a potential divider coupled between the terminals and having a tapping point; and a differential amplifier having a first input coupled to the tapping point, a second input coupled to a point of reference potential, and an output coupled to an output of the d.c. balance control means.
two terminals for coupling to a two-wire telephone subscriber line;
two controlled current circuits (CCCs) for respectively supplying direct current to and sinking direct current from the line via the terminals;
a feedback loop responsive to direct current on the line for controlling the CCCs; and d.c. balance control means responsive to a d.c. imbalance of potentials at the terminals for controlling the feedback loop to modify control of the CCCs to reduce the d.c. imbalance;
the d.c. balance control means comprising:
a potential divider coupled between the terminals and having a tapping point; and a differential amplifier having a first input coupled to the tapping point, a second input coupled to a point of reference potential, and an output coupled to an output of the d.c. balance control means.
2. A SLIC as claimed in claim 1 wherein the feedback loop comprises:
means for producing a sum current dependent upon a sum of direct currents flowing via the terminals;
current splitting means for splitting the sum current into two control currents; and means for controlling the two CCCs each in dependence upon a respective one of the two control currents;
wherein the current splitting means is responsive to the output of the d.c. balance control means to control the relative proportions of the two control currents.
means for producing a sum current dependent upon a sum of direct currents flowing via the terminals;
current splitting means for splitting the sum current into two control currents; and means for controlling the two CCCs each in dependence upon a respective one of the two control currents;
wherein the current splitting means is responsive to the output of the d.c. balance control means to control the relative proportions of the two control currents.
3. A SLIC as claimed in claim 2 wherein the current splitting means comprises two transistors having bases coupled respectively to the output of the d.c. balance control means and to a point of reference potential, and having emitters coupled together and supplied with the sum current, and means for deriving the two control currents from collectors of the transistors,
4. A SLIC as claimed in claim 1,2 or 3 wherein the d.c.
balance control means further comprises low pass filter means coupled between the output of the differential amplifier and the output of the d.c. balance control means.
balance control means further comprises low pass filter means coupled between the output of the differential amplifier and the output of the d.c. balance control means.
5. A SLIC as claimed in claim 1 or 2 wherein the first input of the differential amplifier is an inverting input, the SLIC
further comprising a resistor and a capacitor coupled in series between each of the terminals and the output of the differential amplifier.
further comprising a resistor and a capacitor coupled in series between each of the terminals and the output of the differential amplifier.
6. A SLIC as claimed in claim 3 wherein the d.c. balance control means further comprises:
low pass filter means coupled between the output of the differential amplifier and the output of the d.c. balance control means;
the first input of the differential amplifier is an inverting input, and the SLIC further comprises a resistor and a capacitor coupled in series between each of the terminals and the output of the differential amplifier.
low pass filter means coupled between the output of the differential amplifier and the output of the d.c. balance control means;
the first input of the differential amplifier is an inverting input, and the SLIC further comprises a resistor and a capacitor coupled in series between each of the terminals and the output of the differential amplifier.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CA000490968A CA1232988A (en) | 1985-09-18 | 1985-09-18 | Subscriber line interface circuit with improved d.c. balance |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CA000490968A CA1232988A (en) | 1985-09-18 | 1985-09-18 | Subscriber line interface circuit with improved d.c. balance |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA1232988A true CA1232988A (en) | 1988-02-16 |
Family
ID=4131417
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA000490968A Expired CA1232988A (en) | 1985-09-18 | 1985-09-18 | Subscriber line interface circuit with improved d.c. balance |
Country Status (1)
| Country | Link |
|---|---|
| CA (1) | CA1232988A (en) |
-
1985
- 1985-09-18 CA CA000490968A patent/CA1232988A/en not_active Expired
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CA1111589A (en) | Direct coupled transformerless hybrid | |
| US4302726A (en) | Current sources | |
| JPS63169865A (en) | Effective impedance line feeding circuit | |
| EP0157520A2 (en) | Analog multiplier with improved linearity | |
| US4727574A (en) | Subscriber line interface circuit with improved d.c. balance | |
| US4275277A (en) | Subscriber line interface circuit for a telephone line | |
| EP0088777A1 (en) | Balanced current multiplier circuit for a subscriber loop interface circuit | |
| EP0134229B1 (en) | Borsht/slic auto balancing technique | |
| CA1232988A (en) | Subscriber line interface circuit with improved d.c. balance | |
| US4588858A (en) | Differential amplifiers and method of differentially driving a two-wire line circuit | |
| US20070003052A1 (en) | Subscriber Line Interface Circuitry with Common Base Audio Isolation Stage | |
| CA1233283A (en) | Subscriber line interface circuit with longitudinal current suppression | |
| US4622441A (en) | Two-wire/four wire communication interface with noise rejection | |
| US4267408A (en) | Arrangement for applying a signal to a transmission line | |
| JPH0634490B2 (en) | Transmission signal suppression circuit for telephone | |
| US4649235A (en) | Telephone circuit with a class-B amplifier output stage | |
| JPS61214655A (en) | Constant current line circuit | |
| US4340869A (en) | Amplifier for use in a line circuit | |
| US4731589A (en) | Constant current load and level shifter circuitry | |
| US4445006A (en) | Four-wire conversion circuit for a telephone subscriber line | |
| EP0056810A1 (en) | Loop sensing circuit for use with a subscriber loop interface circuit | |
| US4302636A (en) | Subscriber's electronic line equipment comprising a two-wire-four-wire conversion circuit for a telephone exchange | |
| GB2132448A (en) | Telephone subscribers' line interface circuit | |
| JP3046601B2 (en) | Common-mode noise removal circuit | |
| JPH0414904B2 (en) |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| MKEX | Expiry |