CN103490178A - Single-channel array receiving antenna based on two-phase code modulation - Google Patents
Single-channel array receiving antenna based on two-phase code modulation Download PDFInfo
- Publication number
- CN103490178A CN103490178A CN201310470806.2A CN201310470806A CN103490178A CN 103490178 A CN103490178 A CN 103490178A CN 201310470806 A CN201310470806 A CN 201310470806A CN 103490178 A CN103490178 A CN 103490178A
- Authority
- CN
- China
- Prior art keywords
- signal
- phase
- antenna
- phase code
- modulation
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Abstract
The invention discloses a single-channel array receiving antenna based on two-phase code modulation. The antenna mainly solves the problems that an existing common array antenna is complex in structure, high in power, large in size, high in price and inconsistent in amplitude phase due to multiple channels. The single-channel array receiving antenna comprises an antenna element (1), a first-level modulation phase shifter (2), a low-noise amplifier (3), a down converter (4), an analog-to-digital converter (5) and a second-level modulation phase shifter (6), wherein two-phase modulation polymerization procession generated by the first-level modulation phase shifter (2) is carried out on a signal received by the antenna element (1), the multi-channel signal is converted to a single-channel signal, the signal sequentially undergoes amplification through the low-noise amplifier (3), frequency mixing through the down converter (4) and quantization coding through the analog-to-digital converter (5), then a digital baseband signal is obtained, the signal undergoes two-phase code orthogonal demodulation generated through the second-level modulation phase shifter (6), and the single-channel signal recovers to be the multi-channel signal. The structure is simple, the size is small, the cost is low, the problem that amplitude phase inconsistence of the common array antenna is solved, and the functions identical with the common array antenna can be achieved.
Description
Technical field
The invention belongs to antenna technical field, particularly single channel array received antenna, particularly a kind ofly modulate by phase Code the single channel array received antenna that polymerization and demodulation recover to realize multi channel signals, can be used for communication and Radar Signal Processing.
Background technology
Array antenna is an important branch in the fields such as communication, signal processing, developed rapidly in the last thirty years, its application relates to numerous military affairs and the national economy fields such as communication, radar, sonar, earthquake, exploration, radio astronomy and biomedical engineering.The array received antenna is that the diverse location in space forms sensor array by a plurality of sensor settings, and utilize this array to be received the spacing wave field, be multiple spot parallel sampling and processing, purpose is to extract signal and the characteristic information thereof that array receives, and suppresses interference and noise or uninterested information simultaneously.Array Signal Processing is different from general signal processing mode, because its array for by certain way, to be arranged in the transducer group on the diverse location of space, is mainly to utilize the spatial domain characteristic of signal to strengthen signal and effectively extract the signal spatial information (si).With traditional single directional transducer, compare, Array Signal Processing has that wave beam is neatly controlled, high signal gain, extremely strong antijamming capability and the high advantages such as space hyperresolution, and its range of application also constantly enlarges.Yet, in actual engineering application, because various errors are inevitable, for example interchannel mutual coupling, width are mutually inconsistent, cause actual array manifold to tend to occur deviation or disturbance to a certain degree, now, common high-resolution spatial spectral estimation algorithm performance can severe exacerbation, even inefficacy.Therefore, array error is a practical bottleneck of high-resolution Estimation of Spatial Spectrum technological direction always, moreover, when signal to noise ratio is relatively lower, very large to Estimation of Spatial Spectrum and other subsequent affect, can produce the inaccurate problem of measuring.So the breakthrough of amplitude-phase consistency and high s/n ratio will be the practical key of array antenna technological direction.
The array received antenna, another major obstacle for systems such as communication, radio frequency perception and radars is the requirement to cost, size, weight, because conventional arrays reception antenna oscillator end requires each unit will have one to include low-converter, ADC, memory and receiver.For the practical application of high frequency, the restricted gender that the major constraints of conventional arrays reception antenna extensibility is the subsidiary electronic equipment volume of each antenna oscillator end, the zone that is particularly useful for heat radiation is very limited.For large-scale array, the relevant design of conventional arrays reception antenna and problem of implementation are the stationary problems of all transceivers in the actual temperature scope, the actual temperature scope includes the local temperature of each receiver, the internal temperature fluctuation that the amplifier of installing as surface causes.Therefore, limited for the volume of array antenna, be to hamper its difficult problem towards high frequency, the development of large-sized array column direction always.
Summary of the invention
The object of the invention is to the deficiency for above-mentioned prior art, propose that a kind of cost is few, size is little, the lightweight single channel array received antenna based on the phase Code modulation, to reduce antenna, be limited to temperature impact, improve passage amplitude-phase consistency and signal to noise ratio.
For achieving the above object, the present invention includes: antenna oscillator, low noise amplifier, low-converter, analog to digital converter is characterized in that:
Be connected with M one-level modulation phase shifter between antenna oscillator and low noise amplifier, produce one group of phase Code for the mode by phase shift, the signal of antenna oscillator output is carried out to bi-phase modulated, and the signal after modulation is carried out to positive crosslinking polymerization processing, wherein, M is the antenna oscillator number;
Described analog to digital converter, its output is connected with M secondary modulation phase shifter, and for generation of phase Code, the single channel signal that analog to digital converter is exported carries out demodulation process, recovers to obtain the multi-path digital baseband signal.
The above-mentioned single channel array received antenna based on the phase Code modulation, is characterized in that, each one-level modulation phase shifter comprises one-level logic module, one-level gating switch and polymerization transport module;
Described one-level logic module, for generation of phase Code code element p
m, and control the one-level gating switch signal is modulated, this p
m={ p
0(t) ... p
m(t) ... p
m-2(t) p
m-1(t) }, wherein, p
m(t) be the phase Code that each antenna oscillator end produces, this phase Code has zero and lacks autocorrelation, and meets mutually orthogonal property, m=0,1,2 ... M-2, M-1, M is the antenna oscillator number;
Described one-level gating switch, modulated for the output signal to antenna oscillator, and the signal after being modulated is: S={ Γ p
0(t) ω
0(t-τ) ... Γ p
m(t) ω
m(t-τ) ... Γ p
m-1(t) ω
m-1(t-τ) }, wherein, Γ is total reflection amplitudes value, τ is signal transmission delay, ω
m(t-τ) is the waveform after signal time delay, m=0,1,2 ... M-2, M-1;
Described polymerization transport module, carry out polymerization for the output signal to the one-level gating switch, obtains aggregate signal S
aggrfor:
The above-mentioned single channel array received antenna based on the phase Code modulation is characterized in that each secondary modulation phase shifter comprises two-level logic module and secondary gating switch;
Described two-level logic module, for generation of phase Code code element q
m, and control the secondary gating switch and signal is carried out to demodulation, this q
m={ q
0(t) ... q
m(t) ... q
m-2(t) q
m-1(t) }, wherein, q
m(t) be the phase Code that each antenna oscillator end produces, this phase Code has zero and lacks autocorrelation, and meets mutually orthogonal property, m=0,1,2 ... M-2, M-1, M is the antenna oscillator number;
Described secondary gating switch, carry out demodulation for the output signal to analog to digital converter, obtains the multichannel baseband signal S after demodulation
demodfor: S
demod={ q
0s
digtal_aggrq
1s
digtal_aggrq
ms
digtal_aggrq
m-1s
digtal_aggr, wherein, S
digtal_aggrfor the output signal of analog to digital converter, m=0,1,2 ... M-2, M-1.
The above-mentioned single channel array received antenna based on the phase Code modulation, is characterized in that described antenna oscillator, the structure that adopts M the identical metal, rod-shaped pipe of size to be arranged in parallel, the length L of each metal tube=k λ, wherein, λ is signal wavelength, and k is coefficient, k=14 or k=12.
The present invention compared with prior art has following advantage:
1, the present invention, owing to using one-level modulation phase shifter to echo-signal polymerization single-pass process, has greatly reduced multichannel and has processed required electronic device, can realize low cost/low section/lower powered array antenna.
2, the present invention, because the phase Code that utilizes quadrature is modulated, demodulation process, has improved the inhibition ability that broad-band interference, arrowband interference or multipath are disturbed, the impact of reduce disturbance on echo signal preferably.
3, the present invention due to carry out the phase Code modulation and utilize orthogonality to carry out demodulation process, make recovering the Ge road receive between signal disturb mutually little with mutual coupling, signal to noise ratio is high, has well solved the amplitude-phase consistency problem.
The accompanying drawing explanation
Fig. 1 is structural representation of the present invention;
Fig. 2 is the antenna oscillator structure chart in the present invention;
Fig. 3 is the reception signal real part schematic diagram of three antenna oscillators in the present invention;
Fig. 4 is the one-level modulation phase shifter structure schematic diagram in the present invention;
Fig. 5 is the secondary modulation phase shifter structure schematic diagram in the present invention;
Fig. 6 is the output signal schematic diagram of one-level modulation phase shifter of the present invention;
Fig. 7 is the output signal schematic diagram of secondary modulation phase shifter of the present invention;
Fig. 8 is emulation array antenna layout of the present invention and target information figure;
Fig. 9 is the angle on target spectral contrast schematic diagram of the present invention and conventional arrays antenna echo signal.
Embodiment
With reference to Fig. 1, the present invention includes: antenna oscillator 1, one-level modulation phase shifter 2, low noise amplifier 3, low-converter 4, analog to digital converter 5 and secondary modulation phase shifter 6.Wherein: M one-level modulation phase shifter 2 is connected between the input of the output of antenna oscillator 1 and low noise amplifier 3, the output of low noise amplifier 3 is connected with the input of low-converter 4, analog to digital converter 5 is connected between the input of the output of low-converter 4 and M secondary modulation phase shifter 6, wherein, M is the antenna oscillator number.The structure of each parts is as follows:
With reference to Fig. 2, described antenna oscillator 1, be comprised of M the identical shaft-like hollow metal tube 11 of size, wherein, and M >=2, M=10 in this example.The parallel equidistant arrangement of these metal tubes, be fixed on T-shaped support bar 12; The length L of each metal tube=k λ, wherein, λ is signal wavelength, and k is coefficient, and k=14 or k=12 all are connected with sensor unit 13 in the cavity of each metal tube, and the output of each sensor unit 13 is connected with an one-level modulation phase shifter 2.Whole antenna oscillator 1 is placed on open space, the port of its each metal tube receives the spatial domain electromagnetic wave signal, this signal is sent to sensor unit 13 by metal tube, sensor unit 13 converts electromagnetic wave signal to the signal of telecommunication, electric signal waveform as shown in Figure 3, wherein Fig. 3 (a) and Fig. 3 (c) are the signal waveform of array antenna edge sensor output, the signal waveform that Fig. 3 (b) is the output of array antenna central sensor.
With reference to Fig. 4, each one-level modulation phase shifter 2 comprises one-level logic module 21, one-level gating switch 22 and polymerization transport module 23;
This one-level logic module 21, its input is connected with the output of antenna oscillator 1, and this module is comprised of the first logical circuit C1 and the first transistor G1, and wherein the first logical circuit C1 adopts resistance, electric capacity, reactance to build; By controlling electric current and the voltage of the first logical circuit C1 output, make the first transistor G1 in conducting or off-state, produce phase Code code element p
m(t), this phase Code has zero and lacks autocorrelation, and meets mutually orthogonal property, m=0,1,2 ... M-2, M-1, M is the antenna oscillator number;
This one-level gating switch 22, built and formed by transistor seconds G2, and its input is connected to one-level logic module 21
Output, by the phase Code code element in one-level logic module 21, make transistor seconds G2 in conducting and off-state, the open and close state of switch, modulated for the output signal to antenna oscillator 1, the signal after being modulated is:
S＝{Γp
0(t)ω
0(t-τ)…Γp
m(t)ω
m(t-τ)…Γp
M-1(t)ω
M-1(t-τ)}，
Wherein, Γ is total reflection amplitudes value, and τ is signal transmission delay, ω
m(t-τ) is the waveform after signal time delay, m=0,1,2 ... M-2, M-1;
This polymerization transport module 23, its output is connected with low noise amplifier 3, this module is comprised of the second logical circuit C2 and the 3rd transistor G3, wherein the second logical circuit C2 adopts resistance, electric capacity, reactance to build, by controlling electric current and the voltage of the second logical circuit C2 output, make the 3rd transistor G3 in conducting or off-state, to realize the gating polymerization of multiple signals, aggregate signal S
aggrfor:
the aggregate signal waveform as shown in Figure 6.
Described low noise amplifier 3, adopt but be not limited to the device of LMP7711 model, and the signal of one-level modulation phase shifter 2 outputs is processed by the amplification of this low noise amplifier 3, obtains the amplifying signal that gains, and this signal outputs to low-converter 4.
Described low-converter 4, adopt but be not limited to the device of LTC5544 model, and the output signal of low noise amplifier 3, by the Frequency mixing processing of low-converter 4, obtains down-conversion signal, and this signal outputs to analog to digital converter 5.
Described analog to digital converter 5, adopt but be not limited to the device of AD10465 model, and the output signal of low-converter is processed by the quantization encoding of analog to digital converter 5, obtains digital signal, and this signal outputs to secondary modulation phase shifter 6.
With reference to Fig. 5, each secondary modulation phase shifter 6 comprises two-level logic module 61 and secondary gating switch 62;
This two-level logic module 61, its input is connected with the output of analog to digital converter 5, and this module is comprised of the 3rd logical circuit C3 and the 4th transistor G4, and wherein the 3rd logical circuit C3 adopts resistance, electric capacity, reactance to build; By controlling electric current and the voltage of the 3rd logical circuit C3 output, make the 4th transistor G4 in conducting or off-state, produce phase Code code element q
m(t), this phase Code has zero and lacks autocorrelation, and meets mutually orthogonal property, m=0,1,2 ... M-2, M-1, M is the antenna oscillator number;
This secondary gating switch 62, built and formed by the 5th transistor G5, and its input is connected to two-level logic module 61
Output, by the phase Code code element in two-level logic module 61, make the 5th transistor G5 in conducting and off-state, the open and close state of switch, carry out demodulation for the output signal to analog to digital converter 5, obtains the multichannel baseband signal S after demodulation
demodfor:
S
demod＝{q
0·S
digtal_aggr?q
1·S
digtal_aggr…q
m·S
digtal_aggr…q
M-1·S
digtal_aggr}，
Wherein, S
digtal_aggroutput signal for analog to digital converter 5, m=0,1,2 ... M-2, M-1, as shown in Figure 7, wherein Fig. 7 (a) and Fig. 7 (c) are the edge gateway signal waveform of secondary modulation phase shifter output to the multichannel baseband signal waveform of secondary modulation phase shifter 6 outputs, the edge gateway signal waveform that Fig. 7 (b) is the output of secondary modulation phase shifter.
Effect of the present invention can further be verified by following emulation.
1. experiment scene:
As shown in Figure 8, it is emulation array antenna layout of the present invention and target information figure, and the position coordinates of antenna of the present invention and conventional arrays reception antenna is all (0,0) km, and array antenna is provided with 10 antenna oscillators; Have 2 targets in simulating scenes, wherein, the angle information of target 1 is made as-45 °, and the angle information of target 2 is made as+and 45 °.
2. experiment content and result:
Receive the reflected signal of two targets by the antenna scanning spatial domain, this scan sector scope is-90 °～+ 90 °.Carry out wave beam formation by the echo-signal of conventional arrays reception antenna and these two kinds of antennas of the present invention respectively, obtain the angle on target power spectrum chart, as shown in Figure 9, the angle on target power spectrum that wherein dotted line in Fig. 9 is the conventional arrays antenna, the solid line of Fig. 9 is angle on target power spectrum of the present invention.
Contrast by Fig. 9 dotted portion and Fig. 9 solid line part can be shown in: the present invention is under the situation of designs simplification, smaller volume, device minimizing, cost, to the angular surveying of target can reach with the conventional arrays antenna same precisely, and can reach same Measurement Resolution.
Claims (4)
1. the single channel array received antenna based on phase Code modulation, comprising: antenna oscillator (1), low noise amplifier (3), low-converter (4), analog to digital converter (5) is characterized in that:
Be connected with M one-level modulation phase shifter (2) between antenna oscillator (1) and low noise amplifier (3), produce one group of phase Code for the mode by phase shift, the signal of antenna oscillator (1) output is carried out to bi-phase modulated, and the signal after modulation is carried out to positive crosslinking polymerization processing, wherein, M is the antenna oscillator number;
Described analog to digital converter (5), its output is connected with M secondary modulation phase shifter (6), and for generation of phase Code, the single channel signal that analog to digital converter (5) is exported carries out demodulation process, recovers to obtain the multi-path digital baseband signal.
2. the single channel array received antenna based on the phase Code modulation according to claim 1, is characterized in that, each one-level modulation phase shifter (2) comprises one-level logic module (21), one-level gating switch (22) and polymerization transport module (23);
Described one-level logic module (21), for generation of phase Code code element p
m, and control one-level gating switch (22) signal is modulated, this p
m={ p
0(t) ... p
m(t) ... p
m-2(t) p
m-1(t) }, wherein, p
m(t) be the phase Code that each antenna oscillator end produces, this phase Code has zero and lacks autocorrelation, and meets mutually orthogonal property, m=0,1,2 ... M-2, M-1, M is the antenna oscillator number;
Described one-level gating switch (22), modulated for the output signal to antenna oscillator (1), and the signal after being modulated is:
S＝{Γp
0(t)ω
0(t-τ)…Γp
m(t)ω
m(t-τ)…Γp
M-1(t)ω
M-1(t-τ)}，
Wherein, Γ is total reflection amplitudes value, and τ is signal transmission delay, ω
m(t-τ) is the waveform after signal time delay, m=0,1,2 ... M-2, M-1;
Described polymerization transport module (23), carry out polymerization for the output signal to one-level gating switch (22), obtains aggregate signal S
aggrfor:
3. the single channel array received antenna based on the phase Code modulation according to claim 1, is characterized in that, each secondary modulation phase shifter (6) comprises two-level logic module (61) and secondary gating switch (62);
Described two-level logic module (61), for generation of phase Code code element q
m, and control secondary gating switch (62) and signal is carried out to demodulation, this q
m={ q
0(t) ... q
m(t) ... q
m-2(t) q
m-1(t) }, wherein, q
m(t) be the phase Code that each antenna oscillator end produces, this phase Code has zero and lacks autocorrelation, and meets mutually orthogonal property, m=0,1,2 ... M-2, M-1, M is the antenna oscillator number;
Described secondary gating switch (62), carry out demodulation for the output signal to analog to digital converter (5), obtains the multichannel baseband signal S after demodulation
demodfor: S
demod={ q
0s
digtal_aggrq
1s
digtal_aggrq
ms
digtal_aggrq
m-1s
digtal_aggr, wherein, S
digtal_aggrfor the output signal of analog to digital converter (5), m=0,1,2 ... M-2, M-1.
4. the single channel array received antenna based on phase Code modulation according to claim 1, it is characterized in that, described antenna oscillator (1), the structure that adopts M the identical metal, rod-shaped pipe of size to be arranged in parallel, the length L of each metal tube=k λ, wherein, λ is signal wavelength, k is coefficient, k=14 or k=12.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201310470806.2A CN103490178B (en) | 2013-10-07 | 2013-10-07 | Based on the single channel array received antenna of phase Code modulation |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201310470806.2A CN103490178B (en) | 2013-10-07 | 2013-10-07 | Based on the single channel array received antenna of phase Code modulation |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN103490178A true CN103490178A (en) | 2014-01-01 |
| CN103490178B CN103490178B (en) | 2016-03-02 |
Family
ID=49830231
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201310470806.2A Active CN103490178B (en) | 2013-10-07 | 2013-10-07 | Based on the single channel array received antenna of phase Code modulation |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN103490178B (en) |
Citations (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2001069053A (en) * | 1999-08-26 | 2001-03-16 | Toshiba Tec Corp | Directional antenna system |
| CN2779733Y (en) * | 2005-04-08 | 2006-05-10 | 中国电子科技集团公司第五十四研究所 | Electronic phase scanning track receiver |
| CN1770660A (en) * | 2004-10-06 | 2006-05-10 | 美国博通公司 | Method and system for disposing signals in receiver |
| CN1813423A (en) * | 2003-06-30 | 2006-08-02 | 英特尔公司 | Method and apparatus to combine radio frequency signals from multiple antennas |
| JP2007081646A (en) * | 2005-09-13 | 2007-03-29 | Toshiba Corp | Transmitting/receiving device |
| CN101132249A (en) * | 2006-08-23 | 2008-02-27 | 中兴通讯股份有限公司 | Broadband multi-carrier frequency receiver without intermediate-frequency SAW filter |
| CN101361336A (en) * | 2006-01-11 | 2009-02-04 | 国际商业机器公司 | Apparatus and method for signal phase control in an integrated radio circuit |
| CN101488782A (en) * | 2009-02-26 | 2009-07-22 | 锐迪科微电子（上海）有限公司 | Signal processing method for Bluetooth transceiving machine and Bluetooth transceiving machine thereof |
| CN101710841A (en) * | 2008-12-09 | 2010-05-19 | 广东通宇通讯设备有限公司 | Radio remote unit of electrically adjustable antenna and electrically adjustable antenna integrating radio remote unit |
| CN101969329A (en) * | 2010-09-30 | 2011-02-09 | 中国科学院国家天文台 | Signal phase difference estimation device and method in antenna aligning array based on circulating cross-correlation |
| CN102520388A (en) * | 2011-11-18 | 2012-06-27 | 天津大学 | Positioning device using phased array principle and in combination with RSSI (Received Signal Strength Indicator) range measuring |
-
2013
- 2013-10-07 CN CN201310470806.2A patent/CN103490178B/en active Active
Patent Citations (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2001069053A (en) * | 1999-08-26 | 2001-03-16 | Toshiba Tec Corp | Directional antenna system |
| CN1813423A (en) * | 2003-06-30 | 2006-08-02 | 英特尔公司 | Method and apparatus to combine radio frequency signals from multiple antennas |
| CN1770660A (en) * | 2004-10-06 | 2006-05-10 | 美国博通公司 | Method and system for disposing signals in receiver |
| CN2779733Y (en) * | 2005-04-08 | 2006-05-10 | 中国电子科技集团公司第五十四研究所 | Electronic phase scanning track receiver |
| JP2007081646A (en) * | 2005-09-13 | 2007-03-29 | Toshiba Corp | Transmitting/receiving device |
| CN101361336A (en) * | 2006-01-11 | 2009-02-04 | 国际商业机器公司 | Apparatus and method for signal phase control in an integrated radio circuit |
| CN101132249A (en) * | 2006-08-23 | 2008-02-27 | 中兴通讯股份有限公司 | Broadband multi-carrier frequency receiver without intermediate-frequency SAW filter |
| CN101710841A (en) * | 2008-12-09 | 2010-05-19 | 广东通宇通讯设备有限公司 | Radio remote unit of electrically adjustable antenna and electrically adjustable antenna integrating radio remote unit |
| CN101488782A (en) * | 2009-02-26 | 2009-07-22 | 锐迪科微电子（上海）有限公司 | Signal processing method for Bluetooth transceiving machine and Bluetooth transceiving machine thereof |
| CN101969329A (en) * | 2010-09-30 | 2011-02-09 | 中国科学院国家天文台 | Signal phase difference estimation device and method in antenna aligning array based on circulating cross-correlation |
| CN102520388A (en) * | 2011-11-18 | 2012-06-27 | 天津大学 | Positioning device using phased array principle and in combination with RSSI (Received Signal Strength Indicator) range measuring |
Also Published As
| Publication number | Publication date |
|---|---|
| CN103490178B (en) | 2016-03-02 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN103558594B (en) | Based on the phased array beam synthetic method of airborne equipment | |
| WO2016202258A1 (en) | Method, device and system for antenna array calibration | |
| US11415692B2 (en) | High-resolution fully polarimetric frequency modulation continuous wave image radar system using RF switch and image processing method therefor | |
| CN106450796B (en) | Array antenna system and antenna calibration method | |
| EP2541679A1 (en) | Wideband beam forming device, wideband beam steering device and corresponding methods | |
| WO2021082147A1 (en) | Modular millimeter wave radar | |
| CN108693511B (en) | Moving target angle calculation method of time division multiplexing MIMO radar | |
| CN111090080B (en) | Ultra-wideband radar single-channel digital beam forming method based on space-time coding array | |
| CN102082591A (en) | Method for forming circular array antenna digital wave beams | |
| CN104777467B (en) | Object detection method based on frequency scan antenna | |
| CN109683146A (en) | A kind of phased array emission calibrating method based on orthogonal coding waveform | |
| CN110824414A (en) | Device and method for estimating angle of arrival | |
| KR102001394B1 (en) | Method of estimating DOA of received signals based on logarithmic-domain antenna array interpolation, and apparatus for the same | |
| Re et al. | FMCW radar with enhanced resolution and processing time by beam switching | |
| CN115097447A (en) | MIMO radar monitoring system and monitoring method based on MIMO radar monitoring system | |
| Chen et al. | The applications and future of synthetic impulse and aperture radar | |
| CN103490164B (en) | Based on the single channel array emitter antenna of phase Code modulation | |
| Kim et al. | Phased array calibration system with high accuracy and low complexity | |
| CN113985345A (en) | Ultra-wideband correction amplitude-phase fusion direction finding method and system | |
| CN217846611U (en) | Radar sensor and electronic device | |
| CN103490178B (en) | Based on the single channel array received antenna of phase Code modulation | |
| CN103490177B (en) | Based on the single channel array received antenna of frequency precoding | |
| CN113204018B (en) | LFMCW-based MIMO radar rapid signal processing method | |
| CN103779659B (en) | Based on the single channel array emitter antenna of frequency precoding | |
| CN103579759A (en) | Method for achieving omni-directional coverage of wave beams of array antenna |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant |