WO2021144828A1

WO2021144828A1 - Converter and antenna device

Info

Publication number: WO2021144828A1
Application number: PCT/JP2020/000797
Authority: WO
Inventors: 凌上田; 優牛嶋; 裕之青山; 石橋　秀則; 丸山　貴史
Original assignee: 三菱電機株式会社
Priority date: 2020-01-14
Filing date: 2020-01-14
Publication date: 2021-07-22
Also published as: JP7113986B2; JPWO2021144828A1

Abstract

A ground conductor (6) has a slot (5) penetrating to an obverse surface (6b) from a portion, on a reverse surface (6a), surrounded by a portion connecting to an opening edge section (2a) of a waveguide (2). A conductor pattern (4) has (an annular line portion 4a) surrounding a removal portion (4c), which is a portion in which a conductor has been removed, and an input/output terminal portion (4b) connecting with the annular line portion (4a). The position of at least a part of the removal portion (4c) on the front surface (3b) of a dielectric substrate (3) corresponds, across the dielectric substrate (6), to the position of at least a part of the slot (5) of the ground conductor (6).

Description

Converter and antenna device

The present disclosure relates to a converter that converts a signal propagating in a waveguide to a signal propagating in a planar circuit, or a signal propagating in a planar circuit to a signal propagating in a waveguide.

Conventionally, a converter that converts a signal propagating in a waveguide to a signal propagating in a planar circuit or a signal propagating in a planar circuit to a signal propagating in a waveguide is known. For example, the transducer connects a waveguide and a microstrip line to convert a signal propagating through the waveguide into a signal propagating through the microstrip line, or from a signal propagating through the microstrip line to a waveguide. Is converted into a signaling signal. Such converters are widely used in antenna devices that transmit high frequency signals in the microwave band or millimeter wave band.

For example, Non-Patent Document 1 describes a converter including a waveguide and a dielectric substrate. The transducer has a waveguide having an opening edge surrounding the opening at one end, a back surface connected to the opening edge of the waveguide, and a surface opposite to the back surface. The waveguide includes a grounding plate, a back surface in contact with the surface of the grounding plate, a dielectric substrate having a front surface opposite to the back surface, and a microstrip line installed on the front surface of the dielectric substrate. The ground plate is provided with an opening, and the opening is provided with a matching patch that electrically couples to the microstrip line via a dielectric substrate. Further, on the front surface of the dielectric substrate, a conductor pattern installed so as to surround the microstrip line is provided.

Further, in the converter described in Non-Patent Document 1, the width from the edge of the conductor pattern to the portion corresponding to the waveguide through the dielectric substrate in the conductor pattern (Fig. 3 of Non-Patent Document 1). C) is approximately one-fourth the length of the wavelength inside the waveguide in the waveguide. As a result, the portion of the conductor pattern corresponding to the waveguide via the dielectric substrate acts as a short-circuit circuit for the parallel plate waveguide and functions as a choke to prevent radio wave leakage from the microstrip line or matching patch. do.

In the converter described in Non-Patent Document 1 described above, the width from the edge of the conductor pattern to the portion corresponding to the waveguide through the dielectric substrate in the conductor pattern is 3/4 of the wavelength in the waveguide. By defining the length of one wavelength, radio wave leakage can be prevented, but reflection occurs for a signal having a wavelength different from the wavelength in the tube. Therefore, there is a problem that the bandwidth of a signal having a relatively small reflection, which is suitable for conversion, is limited and narrowed.

In a converter with such a narrow bandwidth, even if the resonance frequency deviates slightly from the intended resonance frequency due to a slight error in the shape of the conductor pattern such as a microstrip line, the conversion efficiency is significantly improved. It will drop.
The present disclosure has been made to solve the above-mentioned problems, and an object of the present invention is to prevent radio wave leakage and to realize a wideband converter.

The converter according to the present disclosure has a waveguide having an opening edge surrounding the opening at one end, a back surface connected to the opening edge of the waveguide, and a side opposite to the back surface. A ground conductor having a surface, a back surface in contact with the surface of the ground conductor, a dielectric substrate having a front surface opposite to the back surface, and a conductor pattern installed on the front surface of the dielectric substrate. Has a slot on the back surface that penetrates the front surface from a portion surrounded by a portion connected to the opening edge of the waveguide, and the conductor pattern is an annular surrounding the removed portion, which is the portion from which the conductor has been removed. It has a line portion and an input / output terminal portion connected to the annular line portion, and at least a part of the removed portion on the front surface of the dielectric substrate is located in the slot of the ground conductor via the dielectric substrate. It is a position corresponding to at least a part of the positions.

According to the present disclosure, a radio wave leakage is prevented and a wide band converter is realized.

It is a top view which shows the structure of the converter which concerns on Embodiment 1. FIG. FIG. 5 is a cross-sectional arrow view showing a cross section of the converter according to the first embodiment cut along the line AA'in FIG. It is a perspective view which shows the structure of the waveguide which concerns on Embodiment 1. FIG. It is a perspective view which shows the structure of the modification of the waveguide which concerns on Embodiment 1. FIG. It is a top view which shows the structure of the conductor pattern which concerns on Embodiment 1. FIG. It is a top view which shows the structure of the modification of the conductor pattern which concerns on Embodiment 1. FIG. It is a top view which shows the structure of the grounding conductor which concerns on Embodiment 1. FIG. It is a top view which shows the structure of the 1st modification of the ground conductor which concerns on Embodiment 1. FIG. It is a top view which shows the structure of the 2nd modification of the ground conductor which concerns on Embodiment 1. FIG. It is a graph which shows the electromagnetic field analysis result of the reflection characteristic and the passage characteristic of the converter which concerns on Embodiment 1. FIG. It is a top view which shows the structure of the converter which concerns on Embodiment 2. FIG. It is a top view which shows the structure of the conductor pattern which concerns on Embodiment 2. FIG. It is a top view which shows the structure of the 1st modification of the conductor pattern which concerns on Embodiment 2. FIG. It is a top view which shows the structure of the conductor pattern which is the 2nd modification of the conductor pattern which concerns on Embodiment 2. FIG. It is a top view which shows the structure of the converter which has the conductor pattern which has two input / output terminals.

Hereinafter, in order to explain the present disclosure in more detail, a mode for carrying out the present disclosure will be described with reference to the accompanying drawings.
Embodiment 1.
FIG. 1 is a top view showing the configuration of the converter 1 according to the first embodiment. FIG. 2 is a cross-sectional arrow view showing a cross section of the converter 1 cut along the line AA'of FIG. The x-axis, y-axis, and z-axis shown in the figure are three axes that are orthogonal to each other. The direction parallel to the x-axis is the x-axis direction, the direction parallel to the y-axis is the y-axis direction, and the direction parallel to the z-axis is the direction parallel to the z-axis. The z-axis direction. Of the x-axis directions, the arrow direction is called the plus x direction, and the direction opposite to the plus x direction is called the minus x direction. Of the y-axis directions, the arrow direction is called the plus y direction, and the direction opposite to the plus y direction is called the minus y direction. Of the z-axis directions, the arrow direction is called the plus z direction, and the direction opposite to the plus z direction is called the minus z direction. In the xy plane, the rotation angle from the x-axis to the y-axis centered on the z-axis is Φ, and in the zx plane, the rotation angle from the z-axis to the x-axis centered on the y-axis is θ.

The converter 1 converts a signal propagating in a waveguide into a signal propagating in a planar circuit, or a signal propagating in a planar circuit into a signal propagating in a waveguide. In addition, in this specification, a plane circuit means a circuit made on the plane of a substrate such as a dielectric. As shown in FIGS. 1 and 2, the converter 1 includes a waveguide 2, a ground conductor 6, a dielectric substrate 3, and a conductor pattern 4. In FIG. 1, the waveguide 2 is hidden by the dielectric substrate 3 and cannot be seen, and is therefore shown by a dotted line.
The waveguide 2 has an opening edge 2a surrounding the opening at one end. The waveguide 2 propagates an electromagnetic wave as a signal.

The ground conductor 6 has a back surface 6a connected to the opening edge 2a of the waveguide 2 and a front surface 6b opposite to the back surface 6a. As described above, the waveguide 2 is electrically short-circuited with respect to the ground conductor 6 by connecting the opening edge 2a of the waveguide 2 and the back surface of the ground conductor 6. That is, the waveguide 2 is grounded.

The grounding conductor 6 is formed by, for example, a conductive metal foil such as a copper foil being crimped to the back surface 3a of the dielectric substrate 3 described later. Alternatively, the ground conductor 6 may be formed by attaching a metal plate to the back surface 3a of the dielectric substrate 3.

Further, the ground conductor 6 has a slot 5 penetrating the front surface 6b from a portion of the back surface 6a surrounded by a portion connected to the opening edge portion 2a of the waveguide 2. In FIG. 1, the slot 5 is hidden by the dielectric substrate 3 and cannot be seen, and is therefore shown by a dotted line.

The dielectric substrate 3 has a back surface 3a in contact with the surface 6b of the ground conductor 6 and a front surface 3b on the opposite side to the back surface 3a. For example, the dielectric substrate 3 is a flat plate-shaped member made of a resin material. In the first embodiment, the dielectric substrate 3 is a single-layer substrate. Alternatively, the dielectric substrate 3 may be a multilayer dielectric substrate composed of a plurality of dielectric substrates. More specifically, for example, the dielectric substrate 3 may be a multilayer dielectric substrate in which a plurality of dielectric substrates and a plurality of conductor substrates are alternately laminated.

The conductor pattern 4 is installed on the front surface 3b of the dielectric substrate 3. The conductor pattern 4 is formed by, for example, a conductive metal foil such as a copper foil being pressure-bonded to the front surface 3b of the dielectric substrate 3 and the metal foil being patterned. Alternatively, the conductor pattern 4 may be formed by attaching a patterned metal plate to the front surface 3b of the dielectric substrate 3.

In the first embodiment, the conductor pattern 4 constitutes a microstrip line. More specifically, in the first embodiment, the conductor pattern 4 constitutes a microstrip line together with the ground conductor 6 described above. Alternatively, the conductor pattern 4 may constitute a strip line or a coplanar line.

When the conductor pattern 4 constitutes a strip line, a further dielectric substrate is installed on the surface of the conductor pattern 4 opposite to the surface in contact with the front surface 3b of the dielectric substrate 3, and the conductor in the further dielectric substrate is provided. An additional ground conductor is installed on the surface opposite to the surface in contact with the pattern 4. When the conductor pattern 4 constitutes a coplanar line, a ground conductor parallel to the conductor pattern 4 is installed on the front surface 3b of the dielectric substrate 3.

The conductor pattern 4 has an annular line portion 4a, which is an annular conductor pattern, and an input / output terminal portion 4b connected to the annular line portion. In the first embodiment, the annular line portion 4a is provided at one end of the conductor pattern 4, and the input / output terminal portion 4b is provided at the other end of the conductor pattern 4. The annular line portion 4a surrounds the removed portion 4c, which is the portion from which the conductor has been removed. The annular line portion 4a is electrically open to the waveguide 2. The input / output terminal portion 4b is connected to another member (not shown). A signal is input to the input / output terminal portion 4b from the other member, and the input signal is propagated to the annular line portion 4a. Alternatively, the input / output terminal portion 4b receives a signal from the annular line portion 4a and outputs the received signal to the other member.

Further, in the first embodiment, between the annular line portion 4a and the input / output terminal portion 4b, the impedance modified portion 4d connected to the annular line portion 4a and the impedance modified portion 4d and the input / output terminal portion 4b are connected, respectively. The impedance transformation portion 4e is provided. The impedance-transformed portion 4d and the impedance-transformed portion 4e transmit signals from the annular line portion 4a to the input / output terminal portion 4b, or transmit signals from the input / output terminal portion 4b to the annular line portion 4a, respectively. Impedance matching is performed so as to be performed.

Next, the configuration relating to the arrangement of the slot 5 of the ground conductor 6 and the removal portion 4c of the annular line portion 4a described above will be described below. The position of at least a part of the removal portion 4c of the annular line portion 4a on the front surface 3b of the dielectric substrate 3 corresponds to the position of at least a part of the slot 5 of the ground conductor 6 via the dielectric substrate 3. Is. In other words, as shown in FIGS. 1 and 2, at least a part of the removed portion 4c of the annular line portion 4a on the front surface 3b of the dielectric substrate 3 is of the ground conductor 6 via the dielectric substrate 3. It is located directly above at least a part of slot 5.

In other words, the above configuration regarding the arrangement of the slot 5 and the removal portion 4c is the front surface of the dielectric substrate 3 when viewed from the direction perpendicular to the front surface 3b and the back surface 3a of the dielectric substrate 3 (z-axis direction). The region occupied by at least a part of the removed portion 4c on 3b overlaps with the region occupied by at least a part of the slot 5 of the ground conductor 6 via the dielectric substrate 3.

Alternatively, in other words, with respect to the above configuration regarding the arrangement of the slot 5 and the removal portion 4c, at least a part of the removal portion 4c of the annular line portion 4a is such that the annular line portion 4a and the slot 5 are electrically coupled to each other. , It is provided at a position on the front surface 3b of the dielectric substrate 3 according to the position of at least a part of the slot 5 of the ground conductor 6.

By arranging the slot 5 and the removal portion 4c as described above, the annular line portion 4a is positioned on the front surface 3b of the dielectric substrate 3 corresponding to at least a part of the positions of the slot 5 of the ground conductor 6. Enclose. As a result, radio wave leakage from a position corresponding to at least a part of the position of the slot 5 of the ground conductor 6 on the front surface 3b of the dielectric substrate 3 is prevented, and the annular line portion 4a and the slot 5 are electrically coupled. Can be strengthened.

Further, the line length of the annular line portion 4a is preferably a length that is several times the natural number of the wavelength inside the waveguide 2. The "line length of the annular line portion 4a" here means the length of one circumference of the annular line portion 4a. With this configuration, the signals orbiting the annular line portion 4a do not cancel each other out, so that the electrical coupling between the annular line portion 4a and the slot 5 can be further strengthened.

More specifically about the above-described configuration regarding the arrangement of the slot 5 and the removal portion 4c, in the first embodiment, as shown in FIG. 1, the overall position of the removal portion 4c on the front surface 3b of the dielectric substrate 3 is This is a position corresponding to a part of the position of the slot 5 of the ground conductor 6 via the dielectric substrate 3.

Alternatively, at least a part of the position of the removed portion 4c on the front surface 3b of the dielectric substrate 3 may be a position corresponding to the entire position of the slot 5 of the ground conductor 6 via the dielectric substrate 3. .. Alternatively, the overall position of the removal portion 4c on the front surface 3b of the dielectric substrate 3 may be a position corresponding to the overall position of the slot 5 of the ground conductor 6 via the dielectric substrate 3.

Next, the details of each of the above members will be described with reference to the drawings. First, the above-mentioned waveguide 2 will be described in detail. FIG. 3 is a perspective view showing the configuration of the waveguide 2. As shown in FIG. 3, the waveguide 2 has an opening edge 2a surrounding the opening at one end. Further, in the first embodiment, the waveguide 2 is a hollow waveguide composed of a metal tube wall surrounding the hollow space.

More specifically, in the first embodiment, the waveguide 2 is a rectangular waveguide having a rectangular cross section (xy cross section) perpendicular to the tube axis. As shown in FIGS. 1 and 3, the cross section is a rectangle having a long side parallel to the y-axis and a short side parallel to the x-axis. The shape of the corner portion of the rectangle may be a shape having a curvature. In other words, the shape of the corner portion of the rectangle may be a rounded shape.
The waveguide 2 may be a circular waveguide having a circular cross-sectional shape perpendicular to the tube axis. Further, at least a part of the hollow space of the waveguide 2 may be filled with a dielectric material.

Further, at least a part of the tube wall of the waveguide 2 may be composed of a plurality of through holes arranged along the tube axis. In that case, for example, the waveguide 2 includes two flat tube walls facing each other and a dielectric filled between the two flat tube walls, each of which is the two flat tubes. It has a plurality of through holes that electrically connect the walls and penetrate the dielectric, and the plurality of through holes function as a tube wall by arranging along the tube axis of the waveguide 2. The "through hole" here means a through hole in which the inner wall is metallized.

Next, a modified example of the waveguide 2 will be described. FIG. 4 is a perspective view showing the configuration of the waveguide 10, which is a modified example of the waveguide 2. As shown in FIG. 4, the waveguide 10 is a ridge waveguide having a protrusion 10b whose wall wall protrudes toward a hollow space. Further, the waveguide 10 has an opening edge portion 10a surrounding the opening at one end thereof, similarly to the waveguide 2. The opening edge portion 10a includes one end of the protrusion 10b. The tube wall of the waveguide 10 shown in FIG. 4 has only one protrusion 10b, but may have a plurality of protrusions 10b.
That is, each of the waveguide 2 and the waveguide 10 may have an opening edge portion surrounding the opening at at least one end thereof, and other configurations are not particularly limited.

Next, the details of the conductor pattern 4 described above will be described. FIG. 5 is a top view showing the configuration of the conductor pattern 4. As shown in FIG. 5, in the first embodiment, the shape of the annular line portion 4a of the conductor pattern 4 has a length in a direction parallel to the lateral direction (y-axis direction) of the strip-shaped input / output terminal portion 4b. The output terminal portion 4b has an elongated shape longer than the length in the direction parallel to the longitudinal direction (x-axis direction). Then, in the first embodiment, the shape of the removed portion 4c surrounded by the annular line portion 4a is rectangular. Alternatively, the shape of the removed portion 4c may be square. Alternatively, the shape of the removed portion 4c may be an H-shape or a polygon other than a quadrangle.

Regardless of the shape of the removed portion 4c as described above, at least a part of the positions of the removed portion 4c on the front surface 3b of the dielectric substrate 3 are located on the ground conductor 6 via the dielectric substrate 3. It is a position corresponding to at least a part of the position of the slot 5 of.

Further, as shown in FIG. 5, one end of the impedance-transformed portion 4d of the conductor pattern 4 is connected to the annular line portion 4a, and the other end is connected to the impedance-transformed portion 4e. The impedance transformation portion 4e has a length in a direction parallel to the lateral direction (y-axis direction) of the connected strip-shaped input / output terminal portion 4b in a direction parallel to the longitudinal direction of the input / output terminal portion 4b (x-axis direction). ) Has a shape longer than the length.

As a result, the impedance-altered portion 4e protrudes from the impedance-modified portion 4d and the input / output terminal portion 4b in the directions parallel to the lateral direction of the input / output terminal portion 4b (plus y-axis direction and minus y-axis direction). For example, the length of the impedance transformation portion 4d in the direction parallel to the longitudinal direction (x-axis direction) of the input / output terminal portion 4b, and the direction of the impedance transformation portion 4e parallel to the lateral direction of the input / output terminal portion 4b. By appropriately adjusting the length (in the y-axis direction), impedance matching can be performed as described above.

In the first embodiment, the configuration in which the conductor pattern 4 has the impedance-transformed portion 4d and the impedance-transformed portion 4e has been described in order to perform impedance matching, but the configuration for performing impedance matching is not limited to this configuration. For example, between the annular line portion 4a and the input / output terminal portion 4b, parallel to the lateral direction of the input / output terminal portion 4b according to the position in the direction parallel to the longitudinal direction (x-axis direction) of the input / output terminal portion 4b. An impedance transformation portion having a multi-stage shape having different lengths in different directions (y-axis direction) may be provided.

In other words, between the annular line portion 4a and the input / output terminal portion 4b, as the direction from the input / output terminal portion 4b toward the annular line portion 4a, the direction parallel to the lateral direction of the input / output terminal portion 4b (y-axis direction). An impedance-transformed portion having a multi-stage shape in which the length of) changes discretely may be provided.

Alternatively, between the annular line portion 4a and the input / output terminal portion 4b, parallel to the lateral direction of the input / output terminal portion 4b according to the position in the direction parallel to the longitudinal direction (x-axis direction) of the input / output terminal portion 4b. An impedance transformation portion having a tapered shape having continuously different lengths in various directions (y-axis direction) may be provided.

In other words, between the annular line portion 4a and the input / output terminal portion 4b, as the direction from the input / output terminal portion 4b toward the annular line portion 4a, the direction parallel to the lateral direction of the input / output terminal portion 4b (y-axis direction). An impedance-transformed portion having a tapered shape in which the length of) continuously changes may be provided.

Next, a modified example of the conductor pattern 4 will be described. FIG. 6 is a top view showing the configuration of the conductor pattern 20, which is a modification of the conductor pattern 4. As shown in FIG. 6, the shape of the removed portion 20b surrounded by the annular line portion 20a of the conductor pattern 20 is a shape that is bent twice. The "bent shape" here means a shape having an angular corner portion due to the removal portion 20b being bent.

More specifically, the annular line portion 20a is parallel to the longitudinal direction of the input / output terminal portion 4b, which is opposite to the input / output terminal portion 4b side from two locations connected to the impedance transformation portion 4d. The direction between the direction (with the x-axis direction) and the direction parallel to the lateral direction (y-axis direction) of the input / output terminal portion 4b (the direction between the minus x-axis direction and the plus y-axis direction, and minus x). It extends in the direction between the axial direction and the minus y-axis direction). As a result, the shape of the removed portion 20b surrounded by the annular line portion 20a of the conductor pattern 20 is bent twice.

In the modified example, the configuration in which the shape of the removed portion 20b shown in FIG. 6 is bent twice has been described, but the shape of the removed portion 20b may be bent once or three times or more. .. Alternatively, the shape of the removed portion 20b may be curved at least once. The "curved shape" here means a shape having a rounded portion (a portion having a curvature) by gradually bending the removed portion 20b along the longitudinal direction.

Also in the modified example, at least a part of the removed portion 20b on the front surface 3b of the dielectric substrate 3 is located at least a part of the slot 5 of the ground conductor 6 via the dielectric substrate 3. Corresponding position.

Next, the details of the ground conductor 6 will be described. FIG. 7 is a top view showing the configuration of the ground conductor 6. As described above, the ground conductor 6 has a slot 5 penetrating from the portion of the back surface 6a surrounded by the portion connected to the opening edge portion 2a of the waveguide 2 to the surface 6b. As shown in FIG. 7, in the first embodiment, the shape of the slot 5 is rectangular. Alternatively, the shape of the slot 5 may be square. Alternatively, the shape of the slot 5 may be a polygon other than a quadrangle.

Regardless of the shape of the slot 5 as described above, at least the position of at least a part of the slot 5 on the ground conductor 6 is the removed portion 4c of the annular line portion 4a via the dielectric substrate 3. It is a position corresponding to at least a part of the positions of.

In FIGS. 1, 2 and 7, only one slot 5 is provided in the ground conductor 6, but the ground conductor 6 has an opening edge 2a of the waveguide 2 on the back surface 6a. A plurality of slots 5 may be provided so as to penetrate the surface 6b from the portion surrounded by the connected portion. Even in that case, the position of at least a part of each slot 5 in the ground conductor 6 is at least a part of the removed portion 4c of the annular line portion 4a on the front surface 3b of the dielectric substrate 3 via the dielectric substrate 3. It is a position corresponding to the position of.

In other words, at least a part of the position of the removal part 4c of the annular line part 4a and at least a part of the position of each slot 5 correspond to each other via the dielectric substrate 3. In other words, when viewed from the direction (z-axis direction) perpendicular to the front surface 3b and the back surface 3a of the dielectric substrate 3, the region occupied by at least a part of the removed portion 4c on the front surface 3b of the dielectric substrate 3 is It overlaps with the region occupied by at least a part of each slot 5 of the ground conductor 6 via the dielectric substrate 3.

Next, a first modification of the ground conductor 6 will be described. FIG. 8 is a top view showing the configuration of the ground conductor 30, which is a first modification of the ground conductor 6. As shown in FIG. 8, the ground conductor 30 has an H-shaped slot 31. Although not shown, in this case as well, the slot 31 penetrates from the portion of the back surface of the ground conductor 30 surrounded by the portion connected to the opening edge 2a of the waveguide 2 to the surface of the ground conductor 30. It is a slot to play. Further, also in this case, at least a position of at least a part of the slot 31 in the ground conductor 30 corresponds to a position corresponding to at least a part of the position of the removal portion 4c of the annular line portion 4a via the dielectric substrate 3. Is.

Next, a second modification of the ground conductor 6 will be described. FIG. 9 is a top view showing the configuration of the ground conductor 40, which is a second modification of the ground conductor 6. As shown in FIG. 9, the ground conductor 40 has a slot 41 that is bent three times. The "bent shape" here means a shape having angular portions due to the slot 41 being bent. More specifically, the shape of the slot 41 has a W shape because it is bent three times.

Although not shown, in this case as well, the slot 41 penetrates from the portion of the back surface of the ground conductor 40 surrounded by the portion connected to the opening edge 2a of the waveguide 2 to the surface of the ground conductor 40. It is a slot to play. Further, also in this case, at least a position of at least a part of the slot 41 in the ground conductor 40 corresponds to a position corresponding to at least a part of the position of the removal portion 4c of the annular line portion 4a via the dielectric substrate 3. Is.

As described above, a plurality of examples of the shape of the removal portion 4c and the shape of the slot 5 have been given, but it is preferable that the shape of the removal portion 4c and the shape of the slot 5 are similar to each other. Thereby, the area where the annular line portion 4a surrounds the position corresponding to at least a part of the positions of the slots 5 of the ground conductor 6 on the front surface 3b of the dielectric substrate 3 can be increased. Therefore, radio wave leakage from a position corresponding to at least a part of the position of the slot 5 of the ground conductor 6 on the front surface 3b of the dielectric substrate 3 is further prevented, and the annular line portion 4a and the slot 5 are electrically coupled. Can be further strengthened.

Next, the operation of the converter 1 will be described. For example, a basic mode signal is input to the waveguide 2, and the waveguide 2 propagates the signal to one end of the waveguide 2 provided with an opening edge 2a. Then, the signal reaching one end of the waveguide 2 is electrically coupled to the slot 5 provided in the ground conductor 6. The signal electrically coupled to the slot 5 is electrically coupled to the annular line portion 4a of the conductor pattern 4 via the dielectric substrate 3. Then, the signal electrically coupled to the annular line portion 4a is propagated to the input / output terminal portion 4b via the impedance transformation portion 4d and the impedance transformation portion 4e.

Alternatively, a signal is input to the input / output terminal portion 4b, and the input / output terminal portion 4b propagates to the annular line portion 4a via the impedance transformation portion 4d and the impedance transformation portion 4e. Then, the signal reaching the annular line portion 4a is electrically coupled to the slot 5 provided in the ground conductor 6 via the dielectric substrate 3. The waveguide 2 propagates the signal electrically coupled to the slot 5 from one end to which the opening edge 2a is provided to the other end.

Next, the effectiveness of the above-mentioned arrangement of the removal portion 4c of the annular line portion 4a and the slot 5 of the ground conductor 6 in the converter 1 according to the first embodiment will be described. FIG. 10 is a graph showing the electromagnetic field analysis results of the reflection characteristics and the passage characteristics of the converter 1. The vertical axis of FIG. 10 shows the gain in which the ratio of the output to the input in the converter 1 is shown in dB, and the horizontal axis of FIG. 10 shows the normalized frequency of the signal input / output in the converter 1. The data D1 shown by the solid line in FIG. 10 is data showing the passage characteristics obtained by electromagnetic field analysis of the structure of the converter 1 shown in FIGS. 1 and 2. The data D2 shown by the broken line in FIG. 10 is data showing the reflection characteristics obtained by electromagnetic field analysis of the structure of the converter 1 shown in FIGS. 1 and 2. The data D1 showing the passing characteristics of the converter 1 quantitatively indicates how much the signal passes as the signal is converted by the converter 1. The data D2 showing the reflection characteristics of the converter 1 quantitatively shows how much the signal is reflected as the signal is converted by the converter 1.

The signal attenuation associated with the conversion by the converter 1 shown by the solid line data D1 in FIG. 10 is described in Fig. It can be seen that it is smaller than 4. The reason for this is that, as described above, the conductor pattern 4 has the annular line portion 4a, and at least a part of the position of the removed portion 4c of the annular line portion 4a on the front surface 3b of the dielectric substrate 3 is dielectric. The position corresponding to at least a part of the position of the slot 5 of the ground conductor 6 via the body substrate 3 prevents radio wave leakage and strengthens the electrical coupling between the annular line portion 4a and the slot 5. Because it is.

Further, as shown by the broken line data D2 in FIG. 10, the bandwidth of -15 dB or less, which is the bandwidth of a signal with relatively small reflection, which is suitable for conversion, is defined in the above-mentioned Fig. It can be seen that it is wider than 4. More specifically, the ratio of the bandwidth of -15 dB or less of the converter 1 to the unit bandwidth of the standardization (the bandwidth of the standardized frequency from 0 to 1) is about 35%, which is the standard. The ratio of the bandwidth of -15 dB or less of the converter of Non-Patent Document 1 to the bandwidth corresponding to the unit bandwidth of normalization is about 3%, and the converter 1 realizes a large bandwidth. .. The reason for this will be explained below.

Non-Patent Document 1 further describes a converter as a prior art, and each of the converters has a plurality of throughs that penetrate a dielectric substrate and electrically connect a ground plate and a conductor pattern. There is a hall. The plurality of through holes function as chokes to prevent radio wave leakage from the microstrip line or the matching patch. Further, in the converter proposed in Non-Patent Document 1, in order to suppress unnecessary radio wave leakage without forming the above-mentioned plurality of through holes, as described above, around the microstrip line. , The width from the edge to the portion corresponding to the waveguide (C of Fig. 3 of Non-Patent Document 1) is approximately one-fourth of the wavelength inside the waveguide in the waveguide. A pattern is provided.

However, as described above, in the converter proposed in Non-Patent Document 1, the above-mentioned width of the conductor pattern for preventing radio wave leakage is defined as a length of one-fourth of the in-tube wavelength in the waveguide. As a result, reflection occurs for a signal having a wavelength different from the wavelength in the tube. Therefore, there is a problem that the bandwidth of a signal having a relatively small reflection, which is suitable for conversion, is limited and narrowed.

On the other hand, in the converter 1 according to the first embodiment, unlike the converter proposed in Non-Patent Document 1, the annular line portion 4a, which is a part of the conductor pattern 4, prevents radio wave leakage. Therefore, in the converter 1 according to the first embodiment, a member that limits the bandwidth, such as the above-mentioned conductor pattern for preventing radio wave leakage described in Non-Patent Document 1, is installed around the conductor pattern 4. No need. As a result, the converter 1 has realized a large bandwidth. Further, as a result, in the converter 1 according to the first embodiment, the dimensions (y-axis direction and) of the conductor pattern 4 on the front surface 3b of the dielectric substrate 3 are compared with the converter proposed in Non-Patent Document 1. Dimensions in the x-axis direction) are reduced. Therefore, the size of the converter 1 can be reduced.

The converter 1 according to the first embodiment described above may be mounted on an antenna device that transmits or receives a signal. As described above, since the converter 1 can prevent radio wave leakage and realize a wide band, even in an antenna device provided with the converter 1, radio wave leakage can be prevented and a wide band can be realized. Further, as described above, since the converter 1 can be miniaturized, the antenna device provided with the converter 1 can also be miniaturized.

As described above, the converter 1 according to the first embodiment is connected to the waveguide 2 having the opening edge 2a surrounding the opening at one end and the opening edge 2a of the waveguide 2. A dielectric substrate having a back surface 6a and a front surface 6b opposite to the back surface 6a, a back surface 3a in contact with the front surface 6b of the ground conductor 6, and a front surface 3b opposite to the back surface 3a. 3 and a conductor pattern 4 installed on the front surface 3b of the dielectric substrate 3, and the ground conductor 6 is surrounded by a portion of the back surface 6a that is connected to the opening edge 2a of the waveguide 2. The conductor pattern 4 has a slot 5 penetrating from the portion to the surface 6b, and the conductor pattern 4 has an annular line portion 4a surrounding the removed portion 4c, which is a portion from which the conductor has been removed, and an input / output terminal portion connected to the annular line portion 4a. With 4b, at least a part of the position of the removed portion 4c on the front surface 3b of the dielectric substrate 3 corresponds to at least a part of the position of the slot 5 of the ground conductor 6 via the dielectric substrate 3. The position.

According to the above configuration, the annular line portion 4a surrounds a position corresponding to at least a part of the position of the slot 5 of the ground conductor 6 on the front surface 3b of the dielectric substrate 3. As a result, radio wave leakage from a position corresponding to at least a part of the position of the slot 5 of the ground conductor 6 on the front surface 3b of the dielectric substrate 3 is prevented, and the annular line portion 4a and the slot 5 are electrically coupled. Can be strengthened.

Further, according to the above configuration, it is not necessary to install a member for limiting the bandwidth around the conductor pattern 4, such as the above-mentioned conductor pattern for preventing radio wave leakage described in Non-Patent Document 1. As a result, a wide band can be realized. That is, it is possible to prevent radio wave leakage and realize a wideband converter.

Further, according to the above configuration, it is not necessary to install a member for limiting the bandwidth around the conductor pattern 4, such as the above-mentioned conductor pattern for preventing radio wave leakage described in Non-Patent Document 1. , The size of the converter 1 can be reduced.

Further, the conductor pattern 4 in the converter 1 according to the first embodiment constitutes any one of a microstrip line, a strip line, and a coplanar line.
According to the above configuration, each of the above effects can be obtained in the converter 1 in which the conductor pattern 4 constitutes a microstrip line, a strip line, or a coplanar line.

Further, the shape of the removed portion 4c surrounded by the annular line portion 4a of the conductor pattern 4 in the converter 1 according to the first embodiment is a rectangle, an H shape, or a polygon.
According to the above configuration, the electrical coupling between the annular line portion 4a surrounding the rectangular, H-shaped, or polygonal removal portion 4c and the slot 5 can be strengthened.

Further, the shape of the removed portion 20b surrounded by the annular line portion 20a of the conductor pattern 20 in the converter 1 according to the first embodiment is a bent or curved shape at least once.
According to the above configuration, the electrical coupling between the annular line portion 4a and the slot 5 surrounding the bent or curved removing portion 20b can be strengthened at least once.

Further, the line length of the annular line portion 4a of the conductor pattern 4 in the converter 1 according to the first embodiment is a natural number multiple of the in-tube wavelength in the waveguide 2.
According to the above configuration, since the signals circulating in the annular line portion 4a do not cancel each other out, the electrical coupling between the annular line portion 4a and the slot 5 can be further strengthened.

Further, the shape of the slot 5 of the ground conductor 6 in the converter 1 according to the first embodiment is rectangular or H-shaped.
According to the above configuration, the electrical coupling between the annular line portion 4a and the rectangular or H-shaped slot 5 can be strengthened.

Further, the dielectric substrate 3 in the converter 1 according to the first embodiment is a multilayer dielectric substrate composed of a plurality of dielectric substrates.
According to the above configuration, the above-mentioned effects can be obtained in the converter 1 in which the dielectric substrate 3 is a multilayer dielectric substrate.

Further, the waveguide 2 in the converter 1 according to the first embodiment is a hollow waveguide composed of a metal tube wall surrounding the hollow space.
According to the above configuration, the above-mentioned effects can be obtained in the converter 1 in which the waveguide 2 is a hollow waveguide.

Further, at least a part of the hollow space of the waveguide 2 in the converter 1 according to the first embodiment is filled with a dielectric material.
According to the above configuration, the above-mentioned effects can be obtained in the converter 1 in which at least a part of the hollow space of the waveguide 2 is filled with a dielectric material.

Further, at least a part of the tube wall of the waveguide 2 in the converter 1 according to the first embodiment is composed of a plurality of through holes arranged along the tube axis.
According to the above configuration, each of the above effects can be achieved in the converter 1 in which at least a part of the tube wall of the waveguide 2 is composed of a plurality of through holes arranged along the tube axis. ..

Further, the waveguide 10 in the converter 1 according to the first embodiment is a hollow waveguide composed of a metal tube wall surrounding a hollow space, and the hollow waveguide has a hollow tube wall. A ridge waveguide having at least one or more protrusions 10b protruding toward space.
According to the above configuration, the above-mentioned effects can be obtained in the converter 1 in which the waveguide 10 is a ridge waveguide.

Further, the antenna device according to the first embodiment includes the converter 1 according to the first embodiment.
According to the above configuration, it is possible to prevent radio wave leakage and realize a wide band in the antenna device. In addition, the antenna device can be miniaturized.

Embodiment 2.
In the second embodiment, a configuration will be described in which the conductor pattern further includes a non-connecting portion that is not connected to the annular line portion and the input / output terminal portion.
Hereinafter, the second embodiment will be described with reference to the drawings. The same reference numerals are given to the configurations having the same functions as those described in the first embodiment, and the description thereof will be omitted.
FIG. 11 is a top view showing the configuration of the converter 50 according to the second embodiment. As shown in FIG. 11, in the converter 50, in addition to the configuration of the converter 1 according to the first embodiment, the conductor pattern 51 further has a non-connected portion 51a and a non-connected portion 51b. Although the waveguide 2, the ground conductor 6, and the dielectric substrate 3 included in the converter 50 are not shown, each configuration of these members includes a conductor provided in the converter 1 according to the first embodiment. This is the same as the waveguide 2, the ground conductor 6, and the dielectric substrate 3. Further, in the second embodiment, the configuration in which the conductor pattern 51 has two non-connected portions of the non-connected portion 51a and the non-connected portion 51b will be described, but the conductor pattern 51 has at least one or more non-connected portions. It suffices to have a part. That is, the conductor pattern 51 may have a single non-connected portion or may have three or more non-connected portions. Since the non-connected portion 51a and the non-connected portion 51b have the same configuration, the non-connected portion 51a will be mainly described in the following description.

The non-connected portion 51a is not connected to the annular line portion 4a and the input / output terminal portion 4b. In addition, "not connected" here means that it is not physically connected. The shape of the non-connecting portion 51a is rectangular. Alternatively, the shape of the non-connecting portion 51a may be square. Alternatively, the shape of the non-connecting portion 51a may be a polygon other than a quadrangle.

Further, at least a part of the non-connected portion 51a on the front surface 3b of the dielectric substrate 3 is a position corresponding to at least a part of the position of the slot 5 of the ground conductor 6 via the dielectric substrate 3. .. Since the non-connected portion 51a is not connected to the annular line portion 4a at least a part of the non-connected portion 51a here, the annular line portion 4a is installed on the front surface 3b of the dielectric substrate 3. It is a position different from the position where it was made.

In other words, the above configuration regarding the arrangement of the non-connecting portion 51a and the slot 5 is viewed from the direction perpendicular to the front surface 3b and the back surface 3a of the dielectric substrate 3 (z-axis direction), the front surface 3b of the dielectric substrate 3 The region occupied by at least a part of the non-connecting portion 51a in the above overlaps with the region occupied by at least a part of the slot 5 of the ground conductor 6 via the dielectric substrate 3.

Alternatively, in other words, regarding the above configuration regarding the arrangement of the non-connecting portion 51a and the slot 5, at least a part of the non-connecting portion 51a of the ground conductor 6 is such that the non-connecting portion 51a and the slot 5 are magnetically coupled. It is provided at a position on the front surface 3b of the dielectric substrate 3 according to the position of at least a part of the slot 5.

By arranging the non-connected portion 51a as described above, the non-connected portion 51a is magnetically coupled to the annular line portion 4a and the slot 5 of the ground conductor 6, and is excited in the opposite phase. The non-connecting portion 51a radiates a radio wave having a phase opposite to that of the radio wave radiated from the annular line portion 4a or the slot 5 into space. Therefore, the radio wave radiated from the non-connected portion 51a and the radio wave radiated from the annular line portion 4a or the slot 5 are canceled in the space, so that the radio wave leakage from the annular line portion 4a or the slot 5 is suppressed and the signal is transmitted. The loss can be reduced.

Further, the line length of the non-connecting portion 51a is preferably a length that is several times the natural number of the in-tube wavelength of the waveguide 2. The "line length" here means the length of the line when the non-connected portion 51a is regarded as a line through which a current flows. With this configuration, the non-connected portion 51a is radiated from the annular line portion 4a or the slot 5 because the reciprocating currents between one end and the other end of the non-connected portion 51a do not cancel each other out. Radio waves of the opposite phase to the radio waves can be efficiently radiated into the space, radio wave leakage can be further suppressed, and signal transmission loss can be further reduced.

The non-connected portion 51b has the same configuration as the non-connected portion 51a described above. The non-connected portion 51a and the non-connected portion 51b are respectively installed on the front surface 3b of the dielectric substrate 3 so as to sandwich the annular line portion 4a between them. Further, the non-connected portion 51a and the non-connected portion 51b are positioned at positions symmetrical with respect to each other on the front surface 3b of the dielectric substrate 3 with respect to the line axis (line AA') of the strip-shaped input / output terminal portion 4b. is set up. Further, the non-connected portion 51a and the non-connected portion 51b are installed at positions symmetrical with respect to each other on the front surface 3b of the dielectric substrate 3 with respect to the center a of the removed portion 4c of the annular line portion 4a. By arranging the non-connected portion 51a and the non-connected portion 51b as described above, it is possible to effectively suppress radio wave leakage from the annular line portion 4a or the slot 5 and reduce the signal transmission loss.

Next, the details of the conductor pattern 51 will be described. FIG. 12 is a top view showing the configuration of the conductor pattern 51. As shown in FIG. 12, the shape of the annular line portion 4a of the conductor pattern 51 is such that the length in the direction parallel to the lateral direction (y-axis direction) of the strip-shaped input / output terminal portion 4b is the length of the input / output terminal portion 4b. It is an elongated shape longer than the length in the direction parallel to the direction (x-axis direction). Here, the length in the direction parallel to the lateral direction (y-axis direction) of the input / output terminal portion 4b in the annular line portion 4a is L1, and parallel to the longitudinal direction of the input / output terminal portion 4b in the annular line portion 4a. If the length in the above direction (x-axis direction) is L2, then L1> L2 holds. That is, the direction (y-axis direction) parallel to the lateral direction of the input / output terminal portion 4b in the annular line portion 4a is the longitudinal direction of the annular line portion 4a, and the input / output terminal portion 4b in the annular line portion 4a. The direction parallel to the longitudinal direction (x-axis direction) is the lateral direction of the annular line portion 4a.

Further, as shown in FIG. 12, the shape of the non-connected portion 51a is such that the length in the direction parallel to the lateral direction (x-axis direction) of the annular line portion 4a is parallel to the longitudinal direction of the annular line portion 4a. It is a rectangle longer than the length in the (y-axis direction). Here, the length of the non-connected portion 51a in the direction parallel to the longitudinal direction (y-axis direction) of the annular line portion 4a is L3, and the direction parallel to the lateral direction of the annular line portion 4a in the non-connected portion 51a. Assuming that the length (in the x-axis direction) is L4, L3 <L4 holds. That is, the direction (y-axis direction) parallel to the longitudinal direction of the annular line portion 4a in the non-connected portion 51a is the lateral direction of the non-connected portion 51a, and the lateral direction of the annular line portion 4a in the non-connected portion 51a. The direction parallel to (x-axis direction) is the longitudinal direction of the non-connecting portion 51a.

Here, when the annular line portion 4a and the non-connected portion 51a are compared, the length L4 of the non-connected portion 51a in the longitudinal direction is longer than the length L2 of the annular line portion 4a in the lateral direction. That is, L4> L2 holds.

The structural difference between the annular line portion 4a and the non-connected portion 51a also holds between the annular line portion 4a and the non-connected portion 51b. Then, one long side of the non-connecting portion 51a faces one short side of the annular line portion 4a on the front surface 3b of the dielectric substrate 3, and one long side of the non-connecting portion 51b is the dielectric substrate. On the front surface 3b of 3, it faces the other short side of the annular line portion 4a. That is, the annular line portion 4a is surrounded between the non-connected portion 51a and the non-connected portion 51b on the front surface 3b of the dielectric substrate 3. As a result, it is possible to effectively suppress radio wave leakage from the annular line portion 4a or the slot 5 and reduce the signal transmission loss.

Next, a first modification of the conductor pattern 51 will be described. FIG. 13 is a top view showing the configuration of the conductor pattern 60, which is a first modification of the conductor pattern 51. As shown in FIG. 13, each shape of the non-connecting portion 60a and the non-connecting portion 60b in the conductor pattern 60 is an H shape. Since the non-connected portion 60a and the non-connected portion 60b have the same configuration, the non-connected portion 60a will be mainly described in the following description.

The shape of the non-connected portion 60a has a different width in the lateral direction depending on the position in the longitudinal direction. More specifically, the shape of the non-connecting portion 60a is a shape in which the width in the lateral direction is discretely different depending on the position in the longitudinal direction.

In the first modification, the non-connecting portion 60a is in a direction parallel to the longitudinal direction of the annular line portion 4a (y-axis) according to the position in the direction parallel to the lateral direction (x-axis direction) of the annular line portion 4a. It has a multi-stage shape with different lengths (directions). More specifically, the non-connecting portion 60a is between a first portion 60c including one end, a second portion 60d including the other end, and between the first portion 60c and the second portion 60d. Has a third portion 60e of. The third portion 60e has a side facing one short side of the annular line portion 4a on the front surface 3b of the dielectric substrate 3. Then, the length of the first portion 60c in the direction parallel to the longitudinal direction of the annular line portion 4a (y-axis direction) and the length of the second portion 60d in the direction parallel to the longitudinal direction of the annular line portion 4a (y-axis direction). The length of the direction) is longer than the length of the third portion 60e in the direction parallel to the longitudinal direction (y-axis direction) of the annular line portion 4a, respectively. That is, the first portion 60c and the second portion 60d project from the side of the third portion 60e facing one short side of the annular line portion 4a. As a result, the first portion 60c, the second portion 60d, and the third portion of the non-connecting portion 60a partially surround the annular line portion 4a.

The non-connected portion 60b located on the other short side side of the annular line portion 4a has the same configuration as the non-connected portion 60a described above. That is, the non-connected portion 60a and the non-connected portion 60b are respectively installed on the front surface 3b of the dielectric substrate 3 so as to partially surround the annular line portion 4a. By arranging the non-connected portion 60a and the non-connected portion 60b as described above, it is possible to effectively suppress radio wave leakage from the annular line portion 4a or the slot 5 and reduce the signal transmission loss.

Further, since the non-connecting portion 60a has portions having different widths in the lateral direction at both ends, such as the first portion 60c and the second portion 60d described above, the non-connecting portion 60a is formed in the longitudinal direction. When adjusting the length of the waveguide 2 to a length corresponding to the wavelength in the tube, the non-connected portion 60a is not as compared with the case where the non-connected portion 60a does not have portions having different widths in the lateral direction at both ends. The length of the connecting portion 60a in the longitudinal direction can be shortened.

As a result, the non-connected portion 60a becomes closer to the annular line portion 4a as a whole. Therefore, the radio wave radiated from the non-connected portion 60a in the opposite phase approaches the annular line portion 4a and the slot 5 of the ground conductor 6, the canceling effect of the radio wave is enhanced, the radio wave leakage is suppressed, and the signal transmission loss is reduced. Can be reduced. This also applies to the non-connected portion 60b.

Next, a second modification of the conductor pattern 51 will be described. FIG. 14 is a top view showing the configuration of the conductor pattern 70, which is a second modification of the conductor pattern 51. As shown in FIG. 14, the conductor pattern 70 has a non-connected portion 70a and a non-connected portion 70b. Since the non-connected portion 70a and the non-connected portion 70b have the same configuration, the non-connected portion 70a will be mainly described in the following description.

The shape of the non-connecting portion 70a is the same as the above-mentioned non-connecting portion 60a and the non-connecting portion 60b, and the width in the lateral direction differs depending on the position in the longitudinal direction. More specifically, the shape of the non-connecting portion 70a is a shape in which the width in the lateral direction is discretely different depending on the position in the longitudinal direction.

In the second modification, the non-connecting portion 70a is in a direction parallel to the longitudinal direction (y-axis) of the annular line portion 4a according to the position in the direction parallel to the lateral direction (x-axis direction) of the annular line portion 4a. It has a multi-stage shape with different lengths (directions).

More specifically, the unconnected portion 70a is connected to a first portion 70c including one end, a second portion 70d including the other end, and a third portion 70e connected to the first portion 70c. , A fourth portion 70f connected to the second portion 70d, and a fifth portion 70g between the third portion 70e and the fourth portion 70f.

The length of the first portion 70c in the direction parallel to the longitudinal direction of the annular line portion 4a (y-axis direction) is the direction parallel to the longitudinal direction of the annular line portion 4a in the third portion 70e (y-axis direction). ) Is longer than the length. Further, the length of the second portion 70d in the direction parallel to the longitudinal direction of the annular line portion 4a (y-axis direction) is the direction parallel to the longitudinal direction of the annular line portion 4a in the fourth portion 70f (y). Longer than the axial length. Further, the length of the third portion 70e in the direction parallel to the longitudinal direction of the annular line portion 4a (y-axis direction) and the length of the fourth portion 70f in the direction parallel to the longitudinal direction of the annular line portion 4a (y-axis direction). The length in the direction) is longer than the length in the direction (y-axis direction) parallel to the longitudinal direction of the annular line portion 4a in the fifth portion 70g. Further, the fifth portion 70g has a side facing one short side of the annular line portion 4a on the front surface 3b of the dielectric substrate 3.

According to the configuration of the above-mentioned second modification, when the length of the non-connecting portion 70a in the longitudinal direction is adjusted to the length corresponding to the wavelength in the tube in the waveguide 2, the above-mentioned first modification is used. The length of the non-connected portion 70a in the longitudinal direction can be further shortened as compared with the non-connected portion 60a. As a result, the non-connected portion 70a becomes even closer to the annular line portion 4a as a whole. Therefore, the radio wave radiated from the non-connected portion 70a in the opposite phase comes closer to the slot 5 of the annular line portion 4a and the ground conductor 6, the canceling effect of the radio wave is further enhanced, the radio wave leakage is further suppressed, and the signal The transmission loss can be further reduced. This also applies to the non-connected portion 70b.

In the first modification and the second modification described above, the shape of the non-connecting portion is such that the width in the lateral direction narrows toward the center between one end and the other end. Although a certain configuration has been described, the shape of the non-connecting portion may be a shape in which the width in the lateral direction becomes wider toward the center between one end portion and the other end portion.

Further, in the first modification and the second modification, the configuration in which the shape of the non-connecting portion has a shape in which the width in the lateral direction is discretely different depending on the position in the longitudinal direction has been described. The shape of the connecting portion may be a tapered shape in which the width in the lateral direction is continuously different depending on the position in the longitudinal direction. That is, the shape of the non-connecting portion may be a shape in which the width in the lateral direction gradually narrows toward the center between one end and the other end, and toward the center, The shape may be such that the width in the lateral direction gradually increases.

The converter 50 according to the second embodiment described above may be mounted on an antenna device that transmits or receives a signal. As a result, in the antenna device, the above-mentioned effects of the converter 50 can be obtained.

As described above, the conductor pattern 51 in the converter 50 according to the second embodiment further has an annular line portion 4a and a non-connecting portion 51a that is not connected to the input / output terminal portion 4b, and is a dielectric substrate 3. At least a part of the position of the non-connecting portion 51a on the front surface 3b is a position corresponding to at least a part of the position of the slot 5 of the ground conductor 6 via the dielectric substrate 3.

According to the above configuration, the non-connected portion 51a is magnetically coupled to the annular line portion 4a and the slot 5 of the ground conductor 6, and is excited in the opposite phase. The non-connecting portion 51a radiates a radio wave having a phase opposite to that of the radio wave radiated from the annular line portion 4a or the slot 5 into space. Therefore, the radio wave radiated from the non-connected portion 51a and the radio wave radiated from the annular line portion 4a or the slot 5 are canceled in the space, so that the radio wave leakage from the annular line portion 4a or the slot 5 is suppressed and the signal is transmitted. The loss can be reduced.

Further, the shape of the non-connecting portion 51a in the converter 50 according to the second embodiment is a rectangle or a polygon.
According to the above configuration, the shape of the non-connecting portion 51a is appropriately made rectangular or polygonal according to the shape of the annular line portion 4a or the shape of the slot 5 of the ground conductor 6, so that the annular line portion is formed. It is possible to suppress the leakage of radio waves from the 4a or the slot 5 and reduce the signal transmission loss.

Further, the shape of the non-connecting portion 60a in the converter 50 according to the second embodiment is a shape in which the length in the lateral direction differs depending on the position in the longitudinal direction.
According to the above configuration, when the length of the non-connected portion 60a in the longitudinal direction is adjusted to a length corresponding to the wavelength in the tube in the waveguide 2, the shape of the non-connected portion 60a is adjusted according to the position in the longitudinal direction. The length of the non-connected portion 60a in the longitudinal direction can be shortened as compared with the case where the lengths in the lateral direction are not different. As a result, the non-connected portion 60a becomes closer to the annular line portion 4a as a whole. Therefore, the radio wave radiated from the non-connected portion 60a in the opposite phase approaches the annular line portion 4a and the slot 5 of the ground conductor 6, the canceling effect of the radio wave is enhanced, the radio wave leakage is suppressed, and the signal transmission loss is reduced. Can be reduced.

Further, the line length of the non-connecting portion 51a in the converter 50 according to the second embodiment is a natural number multiple of a half wavelength of the wavelength in the waveguide 2.

According to the above configuration, since the currents reciprocating between one end and the other end of the non-connecting portion 51a do not cancel each other out, the non-connecting portion 51a is connected from the annular line portion 4a or the slot 5. Radio waves of the opposite phase to the radiated radio waves can be efficiently radiated into space, radio wave leakage can be further suppressed, and signal transmission loss can be further reduced.

In the first and second embodiments described above, the configuration in which the conductor pattern 4 or the conductor pattern 51 has only one input / output terminal portion 4b connected to the annular line portion 4a has been described. However, the conductor pattern 4 or the conductor pattern 51 may further have an input / output terminal portion similar to the input / output terminal portion 4b connected to the annular line portion 4a.

FIG. 15 is a top view showing the configuration of the converter 80 including the conductor pattern 81 further having the same input / output terminal portions as the input / output terminal portions 4b. The conductor pattern 81 of the converter 80 further includes an impedance-transformed portion 81a connected to the annular line portion 4a, an impedance-modified portion 81b connected to the impedance-modified portion 81a, and an input / output terminal portion 81c connected to the impedance-modified portion 81b. .. The impedance-transformed portion 81a has the same configuration as the impedance-modified portion 4d described above, the impedance-modified portion 81b has the same configuration as the impedance-modified portion 4e described above, and the input / output terminal portion 81c has the same configuration as described above. It has the same configuration as the input / output terminal portion 4b of.

Further, the input / output terminal portion 4b and the input / output terminal portion 81c are parallel to each other in the longitudinal direction of the annular line portion 4a on the front surface 3b of the dielectric substrate 3 and are the centers of the annular line portion 4a and the removal portion 4c. It is installed at a position symmetrical with respect to the axis BB'passing through. Further, the impedance-modified portion 4d and the impedance-modified portion 81a are parallel to each other in the longitudinal direction of the annular line portion 4a on the front surface 3b of the dielectric substrate 3 and pass through the centers of the annular line portion 4a and the removal portion 4c. It is installed at a line-symmetrical position with respect to the axis BB'. Further, the impedance-modified portion 4e and the impedance-modified portion 81b are parallel to each other in the longitudinal direction of the annular line portion 4a on the front surface 3b of the dielectric substrate 3 and pass through the centers of the annular line portion 4a and the removal portion 4c. It is installed at a line-symmetrical position with respect to the axis BB'.

As described above, even if a plurality of input / output terminal portions 4b are connected to the annular line portion 4a, it is possible to prevent radio wave leakage and realize a wideband converter.
It is possible to freely combine the embodiments, modify any component of each embodiment, or omit any component in each embodiment.

The converter according to the present disclosure can be used as an antenna device in order to prevent radio wave leakage and realize a wideband converter.

1 converter, 2 waveguide, 2a opening edge, 3 dielectric substrate, 3a back, 3b front, 4 conductor pattern, 4a annular line part, 4b input / output terminal part, 4c removal part, 4d impedance transformation part, 4e Impedance transformation part, 5 slots, 6 ground conductors, 6a back side, 6b front side, 10 waveguides, 10a opening edges, 10b protrusions, 20 conductor patterns, 20a annular conductor parts, 20b removal parts, 30 ground conductors, 31 slots , 40 ground conductor, 41 slot, 50 converter, 51 conductor pattern, 51a non-connecting part, 51b non-connecting part, 60 conductor pattern, 60a non-connecting part, 60b non-connecting part, 60c first part, 60d second Part, 60e 3rd part, 70 conductor pattern, 70a non-connecting part, 70b non-connecting part, 70c 1st part, 70d 2nd part, 70e 3rd part, 70f 4th part, 70g 5th Part, 80 converter, 81 conductor pattern, 81a impedance transformation part, 81b impedance transformation part, 81c input / output terminal part.

Claims

A waveguide having an opening edge surrounding the opening at one end,
A grounding conductor having a back surface connected to the opening edge of the waveguide and a surface opposite to the back surface,
A dielectric substrate having a back surface in contact with the surface of the ground conductor and a front surface opposite to the back surface.
With a conductor pattern installed on the front surface of the dielectric substrate,
The ground conductor has a slot on the back surface that penetrates the front surface from a portion surrounded by a portion of the waveguide that is connected to the opening edge.
The conductor pattern has an annular line portion surrounding the removed portion, which is a portion from which the conductor has been removed, and an input / output terminal portion connected to the annular line portion.
The position of at least a part of the removed portion on the front surface of the dielectric substrate is a position corresponding to the position of at least a part of the slot of the ground conductor via the dielectric substrate. And the converter.
The converter according to claim 1, wherein the conductor pattern constitutes any one of a microstrip line, a strip line, and a coplanar line.
The converter according to claim 1, wherein the shape of the removed portion surrounded by the annular line portion is rectangular, H-shaped, or polygonal.
The converter according to claim 1, wherein the shape of the removed portion surrounded by the annular line portion is a bent or curved shape at least once.
The converter according to claim 1, wherein the line length of the annular line portion is a natural number several times the wavelength in the tube of the waveguide.
The converter according to claim 1, wherein the slot of the ground conductor has a rectangular or H-shaped shape.
The converter according to claim 1, wherein the dielectric substrate is a multilayer dielectric substrate composed of a plurality of dielectric substrates.
The converter according to claim 1, wherein the waveguide is a hollow waveguide composed of a metal tube wall surrounding a hollow space.
The converter according to claim 8, wherein at least a part of the hollow space is filled with a dielectric material.
The converter according to claim 8, wherein at least a part of the pipe wall is composed of a plurality of through holes arranged along the pipe axis.
The converter according to claim 8, wherein the hollow waveguide is a ridge waveguide having at least one protrusion protruding toward the hollow space.
The conductor pattern further includes a non-connecting portion that is not connected to the annular line portion and the input / output terminal portion.
The position of at least a part of the non-connecting portion on the front surface of the dielectric substrate is a position corresponding to the position of at least a part of the slot of the ground conductor via the dielectric substrate. The converter according to claim 1, wherein the converter is characterized.
The converter according to claim 12, wherein the shape of the non-connected portion is a rectangle or a polygon.
The converter according to claim 12, wherein the shape of the non-connected portion is a shape having a different length in the lateral direction depending on the position in the longitudinal direction.
The converter according to claim 12, wherein the line length of the non-connected portion is a natural number multiple of a half wavelength of the wavelength in the waveguide.
An antenna device including the converter according to claim 1.