JPH05110616A - Automatic interference removing device - Google Patents
Automatic interference removing deviceInfo
- Publication number
- JPH05110616A JPH05110616A JP3060847A JP6084791A JPH05110616A JP H05110616 A JPH05110616 A JP H05110616A JP 3060847 A JP3060847 A JP 3060847A JP 6084791 A JP6084791 A JP 6084791A JP H05110616 A JPH05110616 A JP H05110616A
- Authority
- JP
- Japan
- Prior art keywords
- signal
- circuit
- interference
- analog
- digital
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Abstract
Description
【0001】[0001]
【産業上の利用分野】本発明は、ディジタルマイクロ波
無線通信の干渉除去装置に利用する。特に、トランスバ
ーサルフィルタを用いた自動干渉除去装置に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention is used in an interference canceller for digital microwave radio communication. In particular, it relates to an automatic interference canceller using a transversal filter.
【0002】[0002]
【従来の技術】近年のディジタルマイクロ波通信では、
周波数有効利用のためにインタリーブ伝送からコチャネ
ル伝送になってきており、このようにして周波数利用効
率を上げると、アナログ無線通信からの干渉(FM干
渉)の問題が生じてくる。この干渉を除去するために種
々のトランスバーサルフィルタを利用した干渉除去手
段、例えば特開昭62-233943 号公報で提案されている。2. Description of the Related Art In recent digital microwave communication,
Since interleaved transmission has been changed to co-channel transmission for effective frequency use, if the frequency use efficiency is increased in this way, the problem of interference from analog wireless communication (FM interference) arises. To remove this interference, an interference removing means utilizing various transversal filters, for example, is proposed in Japanese Patent Laid-Open No. 62-233943.
【0003】従来例を図2を用いて説明する。図中の→
はN(またはZN:Nはある整数)ビットのディジタル
信号であることを示す。端子1から入力されたディジタ
ル変調信号は二分岐されてそれぞれ掛算器3および4に
入力され、搬送波再生回路17の出力とこの出力に対して
位相がπ/2(90°)遅れた搬送波で直交同期検波を行
い、低域ろ波器9、10で高調波成分を除去した後に、そ
れぞれアナログ・ディジタル変換回路13および14で送信
側で送られたP、Qチャネルのデータ信号がアナログ干
渉により誤りのあるP、Qチャネルのディジタル信号と
して識別再生される。一方、干渉源になるアナログ信号
は端子2から入力され、二分岐されて掛算器5および6
に入力され、復調回路100 で直交同期検波する搬送波と
同一位相となるように移相器19で位相が調整された搬送
波で直交同期検波を行い、低域ろ波器9および10と同一
特性の低域ろ波器11および12で高調波成分を除去した後
に、それぞれアナログ・ディジタル変換回路15および16
により干渉源となるアナログ信号の同相成分および直交
成分は量子化される。これらの量子化された信号はディ
ジタル掛算器21〜24に入力され、またこれらの量子化さ
れた信号の最上位 (Most Significant Bit) ビットは、
象限判定信号DP およびDQ として自動干渉除去回路用
の制御信号発生回路102 に入力される。ディジタル掛算
器21〜24では、自動干渉除去回路用の制御信号発生回路
102 の出力である同相干渉用制御信号ROP、ROQおよび
直交干渉用制御信号IOP、IOQとアナログ・ディジタル
変換回路15および16の出力とそれぞれディジタル掛算が
行われ、その結果がディジタル加算器35または36に出力
される。ディジタル加算器35(36)はディジタル掛算器21
と23 (22と24) をディジタル加算器33 (34) に出力し、
ここでアナログ・ディジタル変換回路13(14)の出力と加
算される。ディジタル加算器33および34の出力のうち、
送信されたデータ信号の次位ビットはそれぞれ誤差信号
EP およびEQ として自動干渉除去回路用の制御信号発
生回路102 に入力される。この誤差信号EP およびEQ
はディジタル変調信号に含まれるアナログ干渉成分を含
む誤差成分に比例した量になる。自動干渉除去回路用の
制御信号発生回路102 の排他的論理和回路25〜28はこれ
らの誤差信号EP およびEQ と象限判定信号DP および
DQ とのそれぞれの相関関係をとり、アップダウン計数
を行う計数回路29〜32で平均化操作が行われ、それぞれ
同相干渉用制御信号ROPおよびROQと直交干渉用制御信
号IOPおよびIOQとが出力される。このようにしてディ
ジタル掛算器21〜24の出力を制御することにより、ディ
ジタル加算器33および34の出力がディジタル信号に含ま
れるアナログ信号による干渉成分の誤差の値が二乗誤差
の意味で最小になることが保証される。また、ディジタ
ル加算器33および34の出力はDCオフセット用の制御信
号発生回路103 に入力され、DCオフセット制御信号OF
FSET(P)および(Q) が作成される。これらのDCオフセ
ット制御信号OFFSET(P) および(Q) によりアナログ・デ
ィジタル変換回路13および14の入力ベースバント信号の
DCオフセットが最適になるように制御される。ここで
DCオフセット用の制御信号発生回路103 はアナログ・
ディジタル変換回路13および14の後に位置させることも
可能であるが、アナログ・ディジタル変換回路13および
14の出力はアナログ干渉成分を含んだディジタル信号で
あるので、制御が不安定になりやすく、通常はアナログ
干渉成分除去後すなわちディジタル加算器33および34の
後に位置する。A conventional example will be described with reference to FIG. In the figure →
Indicates that it is an N (or ZN: N is an integer) bit digital signal. The digital modulation signal input from the terminal 1 is branched into two and input to the multipliers 3 and 4, respectively, and is orthogonal to the output of the carrier recovery circuit 17 and the carrier whose phase is delayed by π / 2 (90 °) with respect to this output. Synchronous detection is performed, and after removing the harmonic components by the low-pass filters 9 and 10, the data signals of the P and Q channels sent on the transmission side by the analog-to-digital conversion circuits 13 and 14 are erroneous due to analog interference. It is identified and reproduced as a digital signal of P and Q channels. On the other hand, the analog signal which becomes the interference source is input from the terminal 2, is branched into two, and is multiplied by the multipliers 5 and 6.
Is input to the demodulation circuit 100, and quadrature synchronous detection is performed on the carrier whose phase is adjusted by the phase shifter 19 so that it has the same phase as the carrier to be quadrature synchronous detected by the demodulation circuit 100. After removing the harmonic components by the low-pass filters 11 and 12, the analog-digital conversion circuits 15 and 16 are respectively
Quantizes the in-phase component and the quadrature component of the analog signal, which are interference sources. These quantized signals are input to the digital multipliers 21 to 24, and the most significant (Most Significant Bit) bits of these quantized signals are
The quadrant determination signals D P and D Q are input to the control signal generation circuit 102 for the automatic interference cancellation circuit. In the digital multipliers 21-24, the control signal generation circuit for the automatic interference cancellation circuit
The in-phase interference control signals R OP and R OQ and the quadrature interference control signals I OP and I OQ which are the outputs of 102 and the outputs of the analog-digital conversion circuits 15 and 16 are respectively digitally multiplied, and the result is digitally added. Output to device 35 or 36. Digital adder 35 (36) is a digital multiplier 21
And 23 (22 and 24) to the digital adder 33 (34),
Here, it is added to the output of the analog / digital conversion circuit 13 (14). Of the outputs of digital adders 33 and 34,
The next significant bits of the transmitted data signal are input to the control signal generating circuit 102 for the automatic interference canceling circuit as error signals E P and E Q , respectively. This error signal E P and E Q
Is an amount proportional to the error component including the analog interference component included in the digital modulation signal. The exclusive OR circuits 25 to 28 of the control signal generating circuit 102 for the automatic interference canceling circuit take the respective correlations between these error signals E P and E Q and the quadrant decision signals D P and D Q, and move up and down. The averaging operation is performed in the counting circuits 29 to 32 for counting, and the in-phase interference control signals R OP and R OQ and the quadrature interference control signals I OP and I OQ are output, respectively. By controlling the outputs of the digital multipliers 21 to 24 in this manner, the error value of the interference component due to the analog signals included in the digital signals of the digital adders 33 and 34 is minimized in the sense of a square error. Is guaranteed. The outputs of the digital adders 33 and 34 are input to the DC offset control signal generation circuit 103, and the DC offset control signal OF
FSET (P) and (Q) are created. These DC offset control signals OFFSET (P) and (Q) are controlled to optimize the DC offset of the input baseband signals of the analog / digital conversion circuits 13 and 14. Here, the control signal generation circuit 103 for DC offset is
Although it can be located after the digital conversion circuits 13 and 14, the analog-digital conversion circuits 13 and
Since the output of 14 is a digital signal containing an analog interference component, the control is likely to be unstable, and is usually located after the analog interference component is removed, that is, after the digital adders 33 and 34.
【0004】[0004]
【発明が解決しようとする課題】このような従来例装置
では、DCオフセットずれによる誤差成分とアナログ干
渉による誤差成分とを共通に用いているので、アナログ
干渉信号の搬送波周波数がディジタル信号の搬送波周波
数の近傍になると、DCオフセットずれによる制御とア
ナログ干渉を除去するための制御とが競合状態になり、
制御が発散する欠点があった。In such a conventional apparatus, since the error component due to the DC offset shift and the error component due to the analog interference are commonly used, the carrier frequency of the analog interference signal is the carrier frequency of the digital signal. In the vicinity of, the control due to the DC offset deviation and the control for removing the analog interference are in a conflicting state,
There was a drawback that the control diverged.
【0005】本発明は、このような欠点を除去するもの
で、ディジタル変調信号の搬送波周波数とアナログ信号
の搬送波周波数との周波数差が小さいときでも安定した
干渉除去が実現できる自動干渉除去装置を提供すること
を目的とする。The present invention eliminates such drawbacks, and provides an automatic interference canceller capable of realizing stable interference cancellation even when the frequency difference between the carrier frequency of a digital modulation signal and the carrier frequency of an analog signal is small. The purpose is to do.
【0006】[0006]
【課題を解決するための手段】本発明は、アナログ信号
で変調された第一被変調搬送波に干渉され、ディジタル
変調信号で変調された第二被変調搬送波を入力する第一
端子と、上記第一被変調搬送波を入力する第二端子と、
上記第二被変調搬送波に対して直交同期検波を施して第
一量子化信号を出力する第一復調回路と、上記第二被変
調搬送波に対して上記第一復調回路と同一位相で直交同
期検波を施して第二量子化信号を出力する第二復調回路
と、上記第一量子化信号から上記第二量子化信号を除去
して第三量子化信号を生成する自動干渉除去回路と、上
記第三量子化信号と上記第二量子化信号とに基づき上記
自動干渉除去回路の制御信号を出力する第一制御信号発
生回路と、与えられた信号に基づき上記第一復調回路に
オフセット制御信号を出力する第二制御信号発生回路と
を備えた自動干渉除去装置において、上記第二量子化信
号を入力し、上記第一被変調搬送波の搬送波周波数と上
記第二被変調搬送波の搬送波周波数との周波数差と閾値
とを比較する周波数差判別回路と、上記周波数差判別回
路の比較結果に基づき上記第三量子化信号または上記第
一量子化信号のいずれか一方を選択して上記第二制御信
号発生回路に与える切替器とを備えたことを特徴とす
る。According to the present invention, there is provided a first terminal for interfering with a first modulated carrier wave modulated by an analog signal and inputting a second modulated carrier wave modulated by a digital modulated signal, and the above-mentioned first terminal. A second terminal for inputting one modulated carrier,
A first demodulation circuit that performs quadrature synchronous detection on the second modulated carrier and outputs a first quantized signal; and a quadrature synchronous detection on the second modulated carrier in the same phase as the first demodulation circuit. A second demodulation circuit that outputs a second quantized signal by applying the above, an automatic interference removal circuit that removes the second quantized signal from the first quantized signal, and generates a third quantized signal; A first control signal generation circuit that outputs a control signal of the automatic interference cancellation circuit based on the three quantized signals and the second quantized signal, and an offset control signal to the first demodulation circuit based on the given signal In the automatic interference canceller having a second control signal generating circuit, the second quantized signal is input and the frequency difference between the carrier frequency of the first modulated carrier and the carrier frequency of the second modulated carrier is input. Frequency to compare with the threshold A difference discriminating circuit and a switcher for selecting one of the third quantized signal or the first quantized signal based on the comparison result of the frequency difference discriminating circuit and supplying the selected second quantized signal to the second control signal generating circuit. It is characterized by
【0007】[0007]
【作用】ディジタル変調信号の搬送波周波数とアナログ
信号の搬送波周波数との周波数差が閾値を下回ると、自
動干渉除去回路の入力側のディジタル信号を自動干渉除
去回路の出力側のディジタル信号の代わりにDCオフセ
ット用制御信号発生回路に与える。これにより、周波数
差が少ないときでも、制御の発散を防止して安定した干
渉除去を行う。When the frequency difference between the carrier frequency of the digital modulation signal and the carrier frequency of the analog signal falls below the threshold value, the digital signal on the input side of the automatic interference canceling circuit is replaced with DC instead of the digital signal on the output side of the automatic interference canceling circuit. It is given to the offset control signal generation circuit. As a result, even when the frequency difference is small, divergence of control is prevented and stable interference removal is performed.
【0008】[0008]
【実施例】以下、本発明の一実施例を図面に基づき説明
する。図1にこの実施例の構成を示すブロック構成図で
ある。この実施例は、図1に示すように、アナログ信号
で変調された第一被変調搬送波に干渉され、ディジタル
変調信号で変調された第二被変調搬送波を入力する端子
1と、上記第一被変調搬送波を入力する端子2と、上記
第二被変調搬送波に対して直交同期検波を施して第一量
子化信号を出力する復調回路100 と、第二被変調搬送波
に対して復調回路100と同一位相で直交同期検波を施し
て第二量子化信号を出力する復調回路101 と、上記第一
量子化信号から上記第二量子化信号を除去して第三量子
化信号を生成する自動干渉除去回路104 と、上記第三量
子化信号と上記第二量子化信号とに基づき自動干渉除去
回路104 の制御信号を出力する第一の制御信号発生回路
102 と、与えられた信号に基づき復調回路100にオフセ
ット制御信号を出力する第二の制御信号発生回路103 と
を備え、さらに、本発明の特徴とする手段として、上記
第二量子化信号を入力し、上記第一被変調搬送波の搬送
波周波数と上記第二被変調搬送波の搬送波周波数との周
波数差と閾値とを比較する周波数差判別回路37と、上記
周波数差判別回路37の比較結果に基づき上記第三量子化
信号または上記第一量子化信号のいずれか一方を選択し
て上記第二の制御信号発生回路103 に与える切替器38と
を備える。DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS An embodiment of the present invention will be described below with reference to the drawings. FIG. 1 is a block diagram showing the configuration of this embodiment. In this embodiment, as shown in FIG. 1, a terminal 1 for inputting a second modulated carrier wave which is interfered with a first modulated carrier wave modulated by an analog signal and modulated by a digital modulated signal, and the first modulated carrier wave Terminal 2 for inputting a modulated carrier wave, demodulation circuit 100 for performing quadrature synchronous detection on the second modulated carrier wave and outputting a first quantized signal, and demodulation circuit 100 for the second modulated carrier wave Demodulation circuit 101 that performs quadrature synchronous detection in phase and outputs a second quantized signal, and automatic interference removal circuit that removes the second quantized signal from the first quantized signal to generate a third quantized signal 104, a first control signal generation circuit for outputting a control signal of the automatic interference cancellation circuit 104 based on the third quantized signal and the second quantized signal.
102, and a second control signal generation circuit 103 for outputting an offset control signal to the demodulation circuit 100 based on a given signal, and further, as a feature of the present invention, the second quantized signal is input. The frequency difference determination circuit 37 for comparing the frequency difference between the carrier frequency of the first modulated carrier wave and the carrier frequency of the second modulated carrier wave and the threshold value, and the frequency difference determination circuit 37 based on the comparison result of the frequency difference determination circuit 37. And a switch 38 for selecting either the third quantized signal or the first quantized signal and supplying the selected second quantized signal to the second control signal generating circuit 103.
【0009】次にこの実施例の動作を説明する。本発明
の復調回路100 および101 と、自動干渉除去回路用の制
御信号発生回路102 と、DCオフセット用の制御信号発
生回路103 と、自動干渉除去回路104 との動作および信
号の流れは従来例に同じである。すなわち、ディジタル
変調信号の搬送波周波数とアナログ信号の搬送波周波数
との周波数差Δfがあらかじめ設定された周波数差より
大きい場合には、アナログ・ディジタル変換回路15、16
に接続された周波数差判別回路37がリセット信号Sel と
して例えば「1」を出力する。このときに、切替器38は
DCオフセット用の制御信号発生回路103 に自動干渉除
去回路104 の出力信号 (すなわち、ディジタル加算器33
および34の出力信号) をそのまま出力するので、この場
合の動作は従来例と同一の動作になる。しかし、周波数
差Δfがあらかじめ設定された周波数より小さくなると
選択信号Sel として「0」を出力し、切替器38の出力と
して自動干渉除去回路104 の入力信号 (すなわち、アナ
ログ・ディジタル変換回路13および14の出力信号) を選
択する。アナログ信号の搬送波周波数がディジタル変調
信号の搬送波周波数に近いので、アナログ干渉がアナロ
グ・ディジタル変換回路13および14の直流バイアスのず
れとなって現れ、DCオフセット用の制御信号発生回路
103 出力であるDCオフセット制御信号OFFSET(P) およ
び(Q) で制御することにより干渉を除去することができ
る。また、自動干渉除去回路104 の出力信号 (ディジタ
ル加算器33および34の出力信号) にはアナログ干渉によ
る誤差成分は含まれておらず、定常時と同じ状態であ
り、自動干渉除去回路用の制御信号発生回路102 もその
ように動作する。Next, the operation of this embodiment will be described. The operations and signal flows of the demodulation circuits 100 and 101 of the present invention, the control signal generation circuit 102 for the automatic interference elimination circuit, the control signal generation circuit 103 for DC offset, and the automatic interference elimination circuit 104 are the same as those of the conventional example. Is the same. That is, when the frequency difference Δf between the carrier frequency of the digital modulation signal and the carrier frequency of the analog signal is larger than the preset frequency difference, the analog-digital conversion circuits 15 and 16 are provided.
The frequency difference discriminating circuit 37 connected to outputs the reset signal Sel, for example, "1". At this time, the switch 38 causes the control signal generating circuit 103 for DC offset to output the output signal of the automatic interference canceling circuit 104 (that is, the digital adder 33
And the output signals of 34) are output as they are, the operation in this case is the same as that of the conventional example. However, when the frequency difference Δf becomes smaller than the preset frequency, “0” is output as the selection signal Sel, and the output of the switch 38 is the input signal of the automatic interference canceling circuit 104 (that is, the analog-digital conversion circuits 13 and 14). Output signal of). Since the carrier frequency of the analog signal is close to the carrier frequency of the digital modulation signal, analog interference appears as a deviation of the DC bias of the analog-digital conversion circuits 13 and 14, and a control signal generation circuit for DC offset is generated.
The interference can be eliminated by controlling the output DC offset control signals OFFSET (P) and (Q). In addition, the output signal of the automatic interference cancellation circuit 104 (output signals of the digital adders 33 and 34) does not include an error component due to analog interference, and is in the same state as in the steady state. The signal generation circuit 102 also operates in this way.
【0010】[0010]
【発明の効果】本発明は、以上説明したように、周波数
差判別回路を設けディジタル変調信号の搬送波周波数と
アナログ信号の搬送波周波数との周波数差がある周波数
差より小さい場合に、DCオフセット用制御信号発生回
路入力として自動干渉除去回路の入力前のディジタル信
号を選択するので、周波数差が小さい場合にも安定して
干渉除去できる効果がある。As described above, the present invention provides the control for DC offset when the frequency difference discriminating circuit is provided and the frequency difference between the carrier frequency of the digital modulation signal and the carrier frequency of the analog signal is smaller than a certain frequency difference. Since the digital signal before being input to the automatic interference canceling circuit is selected as the input of the signal generating circuit, there is an effect that the interference can be stably canceled even when the frequency difference is small.
【図1】 本発明実施例の構成を示すブロック構成図。FIG. 1 is a block diagram showing the configuration of an embodiment of the present invention.
【図2】 従来例の構成を示すブロック構成図。FIG. 2 is a block configuration diagram showing a configuration of a conventional example.
1、2 端子 3〜6 掛算器 7、8 π/2移相器 9〜12 低域ろ波器 13〜16 アナログ・ディジタル変換回路 17 搬送波再生回路 18 クロック再生回路 19、20 移相器 21〜24 ディジタル掛算回路 25〜28 排他的論理回路 29〜32 計数回路 33〜36 ディジタル加算器 37 周波数差判別回路 38 切替器 100 、101 復調回路 102 、103 制御信号発生回路 104 自動干渉除去回路 1, 2 Terminals 3 to 6 Multiplier 7, 8 π / 2 Phase shifter 9 to 12 Low-pass filter 13 to 16 Analog-digital conversion circuit 17 Carrier recovery circuit 18 Clock recovery circuit 19, 20 Phase shifter 21 to 24 Digital multiplying circuit 25 to 28 Exclusive logic circuit 29 to 32 Counting circuit 33 to 36 Digital adder 37 Frequency difference determining circuit 38 Switching device 100, 101 Demodulating circuit 102, 103 Control signal generating circuit 104 Automatic interference canceling circuit
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【手続補正書】[Procedure amendment]
【提出日】平成4年10月7日[Submission date] October 7, 1992
【手続補正1】[Procedure Amendment 1]
【補正対象書類名】図面[Document name to be corrected] Drawing
【補正対象項目名】全図[Correction target item name] All drawings
【補正方法】変更[Correction method] Change
【補正内容】[Correction content]
【図1】 [Figure 1]
【図2】 [Fig. 2]
Claims (1)
送波に干渉され、ディジタル変調信号で変調された第二
被変調搬送波を入力する第一端子と、 上記第一被変調搬送波を入力する第二端子と、 上記第二被変調搬送波に対して直交同期検波を施して第
一量子化信号を出力する第一復調回路と、 上記第二被変調搬送波に対して上記第一復調回路と同一
位相で直交同期検波を施して第二量子化信号を出力する
第二復調回路と、 上記第一量子化信号から上記第二量子化信号を除去して
第三量子化信号を生成する自動干渉除去回路と、 上記第三量子化信号と上記第二量子化信号とに基づき上
記自動干渉除去回路の制御信号を出力する第一制御信号
発生回路と、 与えられた信号に基づき上記第一復調回路にオフセット
制御信号を出力する第二制御信号発生回路とを備えた自
動干渉除去装置において、 上記第二量子化信号を入力し、上記第一被変調搬送波の
搬送波周波数と上記第二被変調搬送波の搬送波周波数と
の周波数差と閾値とを比較する周波数差判別回路と、 上記周波数差判別回路の比較結果に基づき上記第三量子
化信号または上記第一量子化信号のいずれか一方を選択
して上記第二制御信号発生回路に与える切替器とを備え
たことを特徴とする自動干渉除去装置。1. A first terminal for receiving a second modulated carrier wave, which is interfered with a first modulated carrier wave modulated by an analog signal and modulated by a digital modulated signal, and a first terminal for inputting the first modulated carrier wave. Two terminals, a first demodulation circuit for performing quadrature synchronous detection on the second modulated carrier and outputting a first quantized signal, and the same phase as the first demodulation circuit for the second modulated carrier. Second demodulation circuit that outputs a second quantized signal by performing quadrature synchronous detection with an automatic interference removal circuit that removes the second quantized signal from the first quantized signal to generate a third quantized signal And a first control signal generation circuit that outputs a control signal of the automatic interference cancellation circuit based on the third quantized signal and the second quantized signal, and an offset to the first demodulation circuit based on a given signal. A second control signal that outputs a control signal In an automatic interference canceller having a signal generation circuit, the second quantized signal is input, and a frequency difference between a carrier frequency of the first modulated carrier and a carrier frequency of the second modulated carrier and a threshold value are set. A frequency difference discriminating circuit to be compared, and a switcher for selecting one of the third quantized signal or the first quantized signal based on the comparison result of the frequency difference discriminating circuit and giving it to the second control signal generating circuit. An automatic interference canceller, comprising:
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP3060847A JP2850557B2 (en) | 1991-01-31 | 1991-01-31 | Automatic interference canceller |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP3060847A JP2850557B2 (en) | 1991-01-31 | 1991-01-31 | Automatic interference canceller |
Publications (2)
Publication Number | Publication Date |
---|---|
JPH05110616A true JPH05110616A (en) | 1993-04-30 |
JP2850557B2 JP2850557B2 (en) | 1999-01-27 |
Family
ID=13154176
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP3060847A Expired - Fee Related JP2850557B2 (en) | 1991-01-31 | 1991-01-31 | Automatic interference canceller |
Country Status (1)
Country | Link |
---|---|
JP (1) | JP2850557B2 (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO1999021334A1 (en) * | 1997-10-20 | 1999-04-29 | Matsushita Electric Industrial Co., Ltd. | Radio communication device and radio communication method |
US6400778B1 (en) | 1997-12-04 | 2002-06-04 | Nec Corporation | DC-offset canceller |
-
1991
- 1991-01-31 JP JP3060847A patent/JP2850557B2/en not_active Expired - Fee Related
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO1999021334A1 (en) * | 1997-10-20 | 1999-04-29 | Matsushita Electric Industrial Co., Ltd. | Radio communication device and radio communication method |
US6493397B1 (en) | 1997-10-20 | 2002-12-10 | Matsushita Electric Industrial Co. Ltd. | Radio communication device and radio communication method |
US6400778B1 (en) | 1997-12-04 | 2002-06-04 | Nec Corporation | DC-offset canceller |
Also Published As
Publication number | Publication date |
---|---|
JP2850557B2 (en) | 1999-01-27 |
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