JP6534904B2 - Terminal station apparatus, method of controlling terminal station apparatus, and method of manufacturing terminal station apparatus - Google Patents

Description

The present invention relates to a terminal station device , a control method for the terminal station device, and a method for manufacturing the terminal station device.

[Foreword]
At present, with the explosive spread of smartphones, microwave resources with high convenience are depleted in frequency resources. As measures, the transition from the 3rd generation mobile phone to the 4th generation mobile phone and the assignment of new frequency bands are being performed. However, since there are many operators who want to provide services, the frequency resources allocated to each operator are limited.

  In the service of mobile phones, studies are underway to improve the frequency utilization efficiency by a multi-antenna system using a plurality of antenna elements. The already widespread wireless standard IEEE (The Institute of Electrical and Electronics Engineers, Inc.) 802.11n uses Multiple Input Multiple Output (MIMO) transmission technology that uses multiple antenna elements for both transmission and reception. Space multiplexing transmission. Thus, in IEEE 802.11n, transmission capacity is increased to improve frequency utilization efficiency. The term "MIMO" is generally used on the assumption that a transmitting station and a receiving station have multiple antenna elements. When the receiving side is a single antenna element, the term MISO (Multiple Input Single Output) is used instead of MIMO. However, in the following, the term MIMO is used in the sense of including all of them.

  In addition, as a recent communication technology, it is divided into a plurality of frequency components (subcarriers) such as orthogonal frequency division multiplexing (OFDM) modulation scheme and SC-FDE (single carrier frequency domain equalization) scheme, and the frequency axis is divided. A system that performs signal processing is common. The following description will be made using the term “subcarrier” on the premise of a general scheme common to OFDM and SC-FDE without particular distinction.

In the MIMO transmission technology, more efficient transmission can be performed by knowing transmission path information between the transmitting station and the receiving station. As the simplest example, the case of multiple antennas on the receiving side has been shown, but in the case of including N antenna elements on the transmitting side and only one antenna element on the receiving side, N antenna elements The directivity control is performed on the transmission side such that the signals to be transmitted are combined in phase by the antenna element on the reception side. This can increase the line gain. Specifically, when channel information from the j-th antenna element of the transmitting station to the antenna element of the receiving station in the k-th subcarrier is h _j ^(k) , The transmission weight w _j ^(k) of ¹⁾ is calculated, and the transmission signal multiplied by this is transmitted from each antenna element (equal gain combining). Note that the channel information in the present specification takes into account the practical circuit configuration and the procedure of signal processing and control, and strictly speaking, an amplifier, a filter, etc. in an RF (Radio Frequency) circuit of a transmitting system and a receiving system. It is assumed that complex phase rotation and amplitude fluctuation information and the like are included.

A vector (h ₁ ^(k) ,..., H _j ^(k) ,..., H _N ^(k) ) having channel information corresponding to each of the first antenna element on the transmitting side to the Nth antenna element as a channel vector h ^It is called ^(k) . Also, vector a transmission weight corresponding from the first antenna element of the transmission side to the N antenna elements and components ^{_{(w 1 (k), ...}} , w j (k), ..., w N (k)) T (T Represents transposition ⁾ is referred to as a transmission weight vector w ^(k) . Strictly speaking, the channel vector in the downlink → h ^(k) (the symbol “→” in front of “h ^(k) ” is a symbol given on h to represent a vector) is a line The vector, transmit weight vector → w ^(k), should be written as a column vector. However, in the following, for the sake of simplicity, the symbol “→” is omitted and the row vector and the column vector are described without distinction. Also, in the following description, the notation relating to the reception signal Rx, the transmission signal Tx and the noise n should be similarly given “→” to clearly indicate that it is a vector, but since there is no misleading notation “→” I omit and explain. The reception signal Rx is given by the following equation (2) for the transmission signal Tx and the noise n.

Substituting equation (1) into equation (2), the value obtained by adding the absolute value of each component h _j ^(k) of channel vector h ^(k) over all antenna components is obtained as a channel gain. If the transmission power from each antenna element is kept the same as in the case of transmission by one antenna, the amplitude of the received signal is N times that in the case of transmission by one antenna element in the case of N antenna elements Expected to be. The received signal power is improved to N ² times since it is proportional to the square of the amplitude. This value is a gain when a plurality of antenna elements are used as an array antenna. Strictly speaking, the gain of the array antenna itself is generally interpreted as N times the received power (as a result of evaluation under a constant total transmission power). Assuming an environment, the description will be made based on the case where the transmission power per element is constant.

  In general, it is known that the increase in transmission capacity with respect to the improvement amount of the signal-noise ratio (SNR) is larger in the low SNR region and smaller in the high SNR region according to Shannon's theorem. Therefore, rather than aiming to improve the transmission capacity by improving the channel gain, the reception side is often provided with a plurality of antenna elements, and the transmission capacity is often aimed to be improved by spatial multiplexing. MIMO transmission technology aims to increase the transmission capacity by spatial multiplexing.

FIG. 1 shows an outline of MIMO transmission. Here, as an explanation focusing on a certain frequency, a suffix “k” representing a subcarrier or a frequency is omitted. In FIG. 1, reference numeral 11 denotes a transmitting station, and reference numeral 12 denotes a receiving station. In this example, both the transmitting station 11 and the receiving station 12 have two antenna elements, and channel information (amplitude, complex phase) between the transmitting antenna # 1 of the transmitting station 11 and the receiving antenna # 1 of the receiving station 12 Information representing the amount of rotation h ₁₁ , channel information between the transmitting antenna # 1 of the transmitting station 11 and the receiving antenna # 2 of the receiving station 12 (information representing the amplitude and amount of rotation of complex phase) h ₂₁ The channel information (information representing the amplitude and the amount of rotation of the complex phase) between the transmitting antenna # 2 of the station 11 and the receiving antenna # 1 of the receiving station 12 is h ₁₂ , the transmitting antenna # 2 of the transmitting station 11 and the receiving station 12 The channel information (amplitude, information representing the amount of rotation of the complex phase) with respect to the receiving antenna # 2 of h is expressed as h _{22 and} signals t ₁ and t ₂ transmitted from two transmitting antennas of the transmitting station 11 , 2 reception of the receiving station 12 Between the signals r ₁ and r ₂ received by the antenna, noise signals n ₁ and n ₂ are used and expressed by the following equation (3).

  Basically, in MIMO transmission, the signal on the transmission side is estimated based on the reception signal on the reception side and the channel matrix. If the noise term in equation (3) is sufficiently small, the transmission signal can be estimated from the reception signal by multiplying both sides by the inverse of the channel matrix. The transmission characteristics can be improved by multiplying the predetermined transmission weight matrix on the transmission side and further multiplying the predetermined reception weight on the reception side, and more efficient transmission becomes possible. For example, when channel information between a plurality of transmitting antenna elements and a receiving antenna element is known, the channel matrix is subjected to singular value decomposition (SVD) and transmission in the eigenmode is performed. Maximize transmission capacity.

  Specifically, the channel matrix H is decomposed into a diagonal matrix D having a unitary matrix U and V and singular values λ as diagonal components as shown in the following equation (4).

  At this time, if a unitary matrix V is used as the transmission weight matrix, the reception signal vector Rx is given by the following equation (5) for the transmission signal vector Tx and the noise vector n.

On the receiving side, the following equation (6) is obtained by multiplying the matrix U ^H of Hermitian conjugates of the unitary matrix U.

In the equation (6), since the non-diagonal components of the diagonal matrix D are zero, the cross terms of the transmission signal are already canceled and the signals are separated. Also, although the noise vector is multiplied by the reception weight matrix U ^H and converted to the noise vector n ′, which is expressed by rotating the coordinate axis and represented, the statistical features of the vector remain equivalent to the original noise vector.

FIG. 2 shows a conceptual diagram of eigenmode transmission. FIG. 2 (a) shows a basic MIMO channel, FIG. 2 (b) shows a situation in which transmission and reception weight matrices are multiplied, and FIG. 2 (c) shows a virtual transmission path formed by eigenmode transmission. It shows. The channel matrix H between the transmitting and receiving antennas of the transmitting station 11 and the receiving station 12 is, as shown in equation (4), a matrix D having singular values λ in each diagonal component by singular value decomposition, and two unitary It is expressed by the product of the matrix U and V ^H. Here, as shown in FIG. 2 (b) and equation (5), when using the transmission weight matrix V on the transmission side and the reception weight matrix U ^H on the reception side, the unitary matrix part of equation (4) is multiplied and united. It becomes a matrix, and as a result, as shown in equation (6), it becomes possible to represent the matrix D with zero non-diagonal components and non-zero diagonal components. This corresponds to a situation in which transmission paths of virtual channels represented by singular values λ ₁ , λ ₂ ... Are parallelly connected, as shown in FIG. 2 (c). At this time, the square value of the absolute value of each singular value λ corresponds to the channel gain of the individual signal sequence. Each singular value λ is a different value for each signal system. The transmission capacity can be maximized by optimizing the transmission mode in accordance with the singular value of the eigenmode. The transmission mode is a specific mode of signal transmission determined by a combination of the modulation multi-level number and the error correction code rate.

  Here, if each component of the channel matrix of the MIMO channel is independent and uncorrelated, the absolute value of each singular value becomes a relatively large value. For example, when there are many reflected waves and the received power of the sight wave is relatively low, each singular value will have a relatively large value as described above. On the other hand, when the transmitting / receiving antenna is in the line-of-sight environment and there is not much reflected wave, only the absolute value of the first singular value is extremely large and the absolute value of the singular value after the second singular value is extremely It tends to be smaller. For this reason, it is generally said that MIMO transmission is suitable for a multipath environment, and not so suitable when the line of sight is dominant.

  The above is a description of a single-user MIMO transmission technology assuming one base station apparatus and one terminal station apparatus. The same description can be extended to multi-user MIMO in which communication is simultaneously performed on the same frequency axis between one base station apparatus and a plurality of terminal stations. In multi-user MIMO, in general, each terminal station apparatus communicates with a smaller number of antenna elements than the total number of signal systems to be spatially multiplexed. Therefore, in the downlink, directivity control is performed in advance for suppressing inter-user interference on the transmission side. Although the specific equation is slightly different, basically, as with the above-mentioned eigenmode transmission, after grasping the channel matrix, a transmission weight in accordance with it is used.

  Further, in the above description, the explanation was made focusing on the downlink, but also in the uplink, it is possible to perform communication using the channel information after grasping the channel information in advance similarly. For example, in the processing as the array antenna described first, in addition to using the in-phase combining weight given by equation (1) as the receiving weight, it is given by the following equation (7) as the maximum ratio combining weight It is also possible to use one.

The constant C in the equation (7) is a coefficient which is appropriately determined. Among the components of the vector, those with large absolute values of h _j ^(k) are added with a large weight, and C is determined such that a small signal is added with a small weight. In this way, a signal with a large SNR is emphasized, and adjustments are made so that the noise of the signal with a low SNR does not excessively affect.

  In addition, although downlink channel information is required to calculate transmission weights, this can be realized by various forms of channel feedback. In the simplest example, the terminal station apparatus can receive a training signal transmitted by the base station apparatus on the downlink, and the reception result can be accommodated in uplink control information and notified. In general, a channel estimation method that performs such loopback is called explicit feedback. Besides this, for example, calibration coefficients necessary for converting uplink channel information and downlink channel information in the base station apparatus are acquired in advance, and channel estimation is performed on the uplink. After that, it is also possible to estimate downlink channel information by multiplying this calibration coefficient. This method is called implicit feedback. Implicit feedback is generally favored for large scale antennas where the number of antennas is huge. However, in the present invention, the method of channel feedback is not particularly limited, and it is assumed that a general channel estimation method can be used.

Future Mobile Network Directions
As described above, with the explosive spread of smartphones, a further increase in transmission capacity is required. In current wireless communication research, technology is being studied for the 5th generation mobile phone following the 4th generation mobile phone, and in this case, 10 times more transmission capacity than the 4th generation is realized. Is required. Here, not only the increase in transmission capacity of one base station apparatus and the wireless system under the control thereof, but also the increase in transmission capacity per unit area are required together. Specifically, in areas where people gather, such as Shinjuku, Shibuya, Ginza and Otemachi, simply increasing the transmission capacity of the wireless system can not cope with it, and reduce the area area covered by one base station device (hereinafter, The same transmission capacity is realized in a smaller area (referred to as “small cell”), and a large number of small cells are set to realize a transmission capacity proportional to the number of small cells. However, since this small cell is required to be installed at a place where people gather and need further transmission capacity, it is not possible to sufficiently design a station as a macro cell having a large area area. Originally, if multiple frequency channels are available to introduce a small cell while the frequency resources are exhausted, it will not utilize that resource as frequency reuse (frequency reuse) but multiple at the same place It is preferable to increase the total transmission capacity by utilizing the frequency channel of Therefore, there is a need for a technology that allows repeated installation of small cells at relatively short distances without station design even with the same frequency channel.

  Furthermore, while the frequency resources of the microwave band are exhausted, it is necessary to secure a certain frequency bandwidth in order to realize a transmission capacity of 10 Gbit / s or more, and for that purpose, utilization of higher frequency bands is expected. Ru. However, since the free space propagation loss increases by 20 dB when the frequency becomes 10 times in line design, the reach of propagation is reduced to 1/10 in the line-of-sight environment with the same transmission power. Furthermore, with regard to increasing the output of the high-power amplifier on the transmission side, the higher the frequency, the harder it becomes, and while limiting the transmission power per antenna, the transmission capacity of 10 Gbit / s or more is enough for line design. Technologies that can be realized are required.

  From such a point of view, large-scale MIMO (Massive MIMO) transmission technology is currently attracting attention. In Massive MIMO transmission technology, the number of antennas on the base station apparatus side is increased by at least one digit or more compared to the conventional MIMO transmission that is several at most and several tens to several hundreds of antenna elements are used Then, the channel gain improvement to the destination terminal station apparatus and the interference to the terminal station apparatus other than the destination are reduced. There are various variations in the implementation method and application method of Massive MIMO, and in the case of a so-called small cell, the reduction of interference to terminal stations other than the destination is utilized for “suppression of inter-cell interference”. Also, as Massive MIMO transmission technology, as in the prior art, of course, simultaneous communication with a plurality of terminal stations is possible in addition to use as single-user MIMO where a large-scale MIMO matrix is simply used in a single terminal station. There is also a use as multi-user MIMO that performs Here, in the case of use as multi-user MIMO, it is possible to utilize a very redundant number of antenna elements for “suppression of inter-user interference” between terminal stations within the same area unlike in the case of small cells. It is. Below, a large scale antenna system (for example, refer nonpatent literature 1 to nonpatent literature 4) is briefly demonstrated as an example of art about these large scale antennas.

[Overview of large scale antenna system]
FIG. 3 is a schematic view of a large scale antenna system. In FIG. 3, a base station apparatus 1, a radio station apparatus 2, a line of sight wave 3, a stable reflection wave 4 by a structure, multiple reflection waves 5 to 6 near the ground, and a structure 7 are shown. In the large-scale antenna system of FIG. 3, the base station device 1 includes a large number (for example, 100 or more) of antenna elements, and is installed at a high place such as a roof of a building or a high steel tower. Similarly, the radio station apparatus 2 is installed at high places such as the roof of a building, on the roof of a house, on a telegraph pole or a steel tower. Therefore, the base station device 1 and the radio station device 2 are generally in a line-of-sight environment, and in addition to the path of the line of sight wave 3 and the path of the stable reflected wave 4 by the large stable structure 7, etc. There are mixed paths of multiple reflection waves 5 and 6 due to moving objects such as cars and people in the vicinity. In addition, especially when using a directional antenna, the reception level of the multiple reflected waves 5 and 6 near the ground becomes lower than that of the line of sight wave 3 and the stable reflected wave 4 or the like.

  FIG. 4 is a diagram showing an impulse response in the line-of-sight environment and the non-line-of-sight environment. FIG. 4 (a) shows an impulse response in a non-line-of-sight environment, and FIG. 4 (b) shows an impulse response in a line-of-sight environment. In FIG. 4A and FIG. 4B, the horizontal axis represents the delay time, and the vertical axis represents the reception level of each delay wave. In the case of the non-line-of-sight environment shown in FIG. 4 (a), there are no direct wave components in the line-of-sight section, many multiple reflected waves of various paths exist as components, and each amplitude and complex phase are randomly and strongly with time. fluctuate.

  On the other hand, when assuming a line-of-sight environment like the large-scale antenna system shown in FIG. 3, the stable path of the stable reflected wave 4 by the line-of-sight 3 and the structure 7 has a high reception level. As shown in FIG. 4 (b), multiple reflected waves of a time-varying path generally have a larger delay amount than the stable reflected wave 4 due to the line-of-sight 3 and the structure 7 due to multiple reflections and attenuation with the path length. The reception level becomes smaller. When such channel information is acquired a plurality of times and averaged, the stable path component has stable values each time in both amplitude and complex phase. However, the components of the time-varying path are randomly combined and averaged on the complex space to approach an average value of zero. Therefore, averaging enables effective extraction of only the stable component. The absolute channel information depends on the symbol timing, and if the symbol timing is different, averaging of channel information can not be appropriately performed.

  In order to solve such a problem, in Non-Patent Document 2, relative channel information (or each channel information divided by the channel information of the reference antenna based on the complex phase of the reference antenna element) is considered. The technology to utilize good) is introduced. If such averaging does not accompany, it is possible to discuss using absolute channel information without using relative channel information, but even in such a case, relative channel information is There is no problem with using it. In the following description, channel information is basically treated as relative channel information based on the complex phase of the reference antenna in order to be comprehensively handled including the averaging process.

  The base station apparatus 1 (see FIG. 3) calculates transmission / reception weights based on the time-independent channel information of stable paths obtained in this manner. The base station apparatus 1 performs directivity control for performing in-phase combination with a large number of antenna elements using the calculated transmission / reception weights. By using the transmission and reception weights described above, the base station apparatus 1 can increase the directivity gain to the radio station apparatus of the communication partner to be the target of directivity control in proportion to the square of the number N of antennas.

Further, since the directivity gain of the interference to the radio station apparatus other than the destination remains N times, a gap of N times in a simple calculation is relatively generated between the desired signal and the interference signal. As a result, the expected value of Signal to Interference Ratio (SIR) is ₁₀ Log ₁₀ (N) [dB]. This expected value is 20 dB when N is 100. Further, if the radio station apparatus with small correlation is selectively spatially multiplexed, further improvement of the SIR characteristic is expected, and higher spatial multiplexing can be realized.

In Non-Patent Document 3 and Non-Patent Document 4, a combination of radio station apparatuses with lower correlation of channel information (channel correlation) and techniques for further suppressing interference which can not be suppressed by the above-mentioned transmission and reception weights is selected. Technology is introduced. In order to realize ultra-high-order spatial multiplexing, it is important to combine radio station apparatuses with small correlation of channel information. A channel vector h _j ^(k) ("h _j ^(k) " is a vector with the channel information on the kth subcarrier between the multiple antenna elements of the base station apparatus and the antenna element of the j-th radio station apparatus being a vector Yes, the symbol “→” should originally be added on h to clearly indicate that it is a vector, but it will be omitted. Hereinafter, it will be omitted similarly in the description below) and another i-th wireless station The channel correlation with the channel vector h _i ^(k) in the device is given by equation (8) below.

The system assumed a sight environment, assuming a virtual channel model consisting only of sight waves, when the correlation of the channel vector h _i between the antenna and the base station apparatus of the radio station apparatus ^_(k) is small In the case where the correlation is large, the situation is not suitable for spatial multiplexing.

[About large-scale MIMO in small cells]
In the description of Equation (8) above, it is assumed that the wireless station apparatus side is a single antenna, and if different wireless station apparatuses, the correlation of the channel vector is generally lowered due to the spatial spread. It was assumed. On the other hand, in the fifth generation mobile phone, a large number of antennas are mounted on the wireless station apparatus side and a large number of antennas are also mounted on the base station apparatus side in order to improve throughput per user. In the recent research report, with the number of antenna elements on the base station side being 256 elements, and the number of antenna elements on the wireless station side being 16 elements, a study was made to increase the capacity by large scale MIMO of 256 × 16 size. There is. Here, it is assumed that the radio station apparatus carried by the user is small in size and portable. Furthermore, for example, in consideration of reducing mutual interference between adjacent small cells, and installation in a place where people concentrate, for example, base stations are installed on the walls of existing buildings (for example, about 20 m above ground level) It is expected that radiation is given to each antenna element to irradiate a limited area in the form of looking down from above. In this case, installing a large antenna on the wall of a building or the like is not preferable from the viewpoints of safety and ease of installation. In the case of using a high frequency band such as a millimeter wave or a quasi-millimeter wave, as the wavelength becomes shorter, miniaturization of the antenna element and formation of directivity of the antenna become easy, and a very narrow area even in the base station device It is expected to use a small antenna set packed with a large number of antennas.

  In this case, if, for example, the channel correlation between the j-th and i-th antenna elements of the plurality of antenna elements in the single radio station apparatus is determined by the above equation (8), the antenna of the radio station apparatus on the user side Under the condition that the element spacing is very short and the line of sight between the base station apparatus and the radio station apparatus can be secured, it can be regarded as a MIMO channel in which the channel correlation between the antenna elements is very large. As described above, when the base station apparatus is installed at a high position such as a wall of a building looking down from the bottom and the user holds a smartphone etc. as a radio station apparatus in hand, the base station apparatus and the radio station apparatus It is expected that the antenna elements between the antenna element and the antenna element will be generally in a line-of-sight environment, and such a situation is expected to be a general use environment.

  In this case, when the MIMO matrix is subjected to singular value decomposition, the absolute value of the first singular value becomes a very high value using the line-of-sight component, but the high order singular values after the second singular value are the first It tends to be very small relatively to the singular value. In other words, as spatial multiplexing transmission utilizing MIMO channels, there is much room for channel gain for the first path corresponding to the first singular value, but for higher order paths higher than the second singular value Is a relatively inefficient situation.

  In order to avoid this problem, for example, it is ideal not to integrate the antenna elements of the base station apparatus in a small-sized housing, but to ensure spatial spread. For example, if the antenna elements of the base station apparatus are assembled in a linear array in which the antenna elements of the base station apparatus are equally arranged in a linear shape of about 10 m, the spatial spread of the antenna elements of the base station apparatus is As the MIMO channel, it can be expected that the absolute value of the high-order singular value higher than the second singular value is increased to contribute to the increase in capacity. However, such a large scale structure is not preferable in terms of the structure of the antenna installation. For example, when the number of antenna elements on the base station apparatus side is 256 elements, individually installing 256 antenna elements at intervals of about 4 cm increases the load of installation work. On the other hand, when a structure assembled in a linear array is installed on the wall of a building, it may be difficult to install it on the wall of the building in order to increase the size of the structure. Furthermore, in order to transmit in a coordinated manner with all the antenna elements, it is necessary to distribute radio frequency signals from one case of a base station apparatus to antenna elements having a spatial extent of about 10 m by a cable, in particular Cable losses in signal transmission in high frequency bands are not negligible. For example, assuming 20 GHz as a radio frequency, a cable loss of 10 dB or more at 10 m may result in loss of acquired line gain due to an increase in the number of antenna elements at the angle.

  For such reasons, in large-scale MIMO operation where line-of-sight waves dominate, it is required to miniaturize at least the antenna on the wireless station apparatus side. Making it difficult.

[Device configuration example of MIMO transmission]
(Whole circuit configuration)
FIG. 5 is a schematic block diagram showing an example of the configuration of base station apparatus 80 in a multi-user MIMO system. Although a multi-user MIMO system will be described here, it can be basically understood that a plurality of antenna elements in the same wireless station apparatus perform a plurality of signal sequences instead of a terminal station apparatus to which spatial multiplexing targets are different. The device configuration is the same as in a single-user MIMO system. As shown in FIG. 5, the base station apparatus 80 includes a transmitter 81, a receiver 85, an interface circuit 87, a MAC (Medium Access Control) layer processing circuit 88, and a communication control circuit 820. The MAC layer processing circuit 88 includes a scheduling processing circuit 881.

  The base station apparatus 80 inputs and outputs data with an external device or a network via the interface circuit 87. The interface circuit 87 detects data to be transferred on the wireless channel among the input data, and outputs the detected data to the MAC layer processing circuit 88. The MAC layer processing circuit 88 performs processing related to the MAC layer in accordance with an instruction of the communication control circuit 820 that performs management control of the entire operation of the base station device 80. Here, the processing relating to the MAC layer includes data input / output by the interface circuit 87, conversion of data transmitted / received on the wireless channel, addition of header information of the MAC layer, and the like. In this process, the scheduling process circuit 881 performs various scheduling processes including a combination of terminal stations that perform space multiplexing simultaneously in multi-user MIMO transmission. The scheduling processing circuit 881 outputs the scheduling result to the communication control circuit 820. In multi-user MIMO, a plurality of signal sequences are output from the MAC layer processing circuit 88 to the transmission unit 81 in order to transmit signals to a plurality of terminal stations at one time.

(Circuit configuration of transmission unit 81)
FIG. 6 is a schematic block diagram showing an example of a configuration of transmission section 81 in base station apparatus 80 in a multi-user MIMO system. As shown in FIG. 6, the transmission unit 81 includes transmission signal processing circuits 811-1 to 811-N _SDM (N _SDM is an integer of 2 or more), and addition synthesis circuits 812-1 to 812-812 _BS-Ant (N _BS-Ant is an integer of 2 or more), IFFT (Inverse Fast Fourier Transform: Inverse Fast Fourier Transform) & GI (Guard Interval: Guard Interval) applying circuit 813-1 to 813-N _BS-Ant , D / A (digital / Analog) converter 814-1 to 814-N _BS-Ant , local oscillator 815, mixers 816-1 to 816-N _BS-Ant , filters 817-1 to 817-N _BS-Ant , high power includes amplifier (HPA) and _{818-1~818-N BS-Ant,} an antenna element _{819-1~819-N BS-Ant,} and a transmission weight processing unit 830 That. The transmission signal processing circuits 811-1 to 811-N _SDM and the transmission weight processing unit 830 are connected to the communication control circuit 820 shown in FIG.

The transmission weight processing unit 830 includes a channel information acquisition circuit 831, a channel information storage circuit 832, and a multi-user MIMO (MU-MIMO) transmission weight calculation circuit 833. Here, _{N SDM} subscript of the transmission signal processing circuit _{811-1~811-N SDM} in FIG. 6 represents a multiplex number for performing spatial multiplexing simultaneously. Further, _{N BS-Ant} subscript circuit from additive synthesis circuit _{812-1~812-N BS-Ant} to the antenna element _{819-1~819-N BS-Ant} is the number of antenna elements provided in the base station apparatus 80 Represents N _BS-Ant is, for example, 100.

In multi-user MIMO, in order to transmit signals to a plurality of terminal stations at one time, signal sequences of a plurality of systems are input from the MAC layer processing circuit 88 to the transmitter 81, and the input signal sequences of a plurality of systems are transmission signals Processing circuits 811-1 to 811-N are input to the _SDM . The transmission signal processing circuit 811-1 to 811-N _SDM receives the data (data input # 1 to #N _SDM ) to be transmitted to each of the destination terminal station apparatuses from the MAC layer processing circuit 88 by the wireless channel. A radio packet to be transmitted is generated and modulation processing is performed. Here, for example, if the use of the OFDM modulation scheme, the transmission signal processing circuit _{811-1~811-N SDM,} performs modulation for each subcarrier to the signal of each signal sequence. Furthermore, the transmission signal processing circuit _{811-1~811-N SDM} multiplies the transmission weight for each subcarrier to a baseband signal which modulation processing has been performed. The signal multiplied by the transmission weight corresponding to each antenna element 819-1 to 819-N _BS-Ant is subjected to the remaining signal processing as necessary, and added and synthesized as sampling data of the transmission signal in the baseband. -1 to 812-N _BS-Ant is input.

The signals input to the adding and combining circuits 812-1 to 812-N _BS-Ant are combined for each subcarrier. The synthesized signal is converted from the signal on the frequency axis to the signal on the time axis by the IFFT & GI application circuits 813-1 to 813-N _BS-Ant , and further insertion of guard intervals or between OFDM symbols (SC-FDE If it is Single-Carrier Frequency Domain Equalization), processing such as waveform shaping between blocks of block transmission is performed, and D / A converter 814-1 is performed for each antenna element 819-1 to 819-N _BS-Ant. At 814-N _BS-Ant , the digital sampling data is converted to a baseband analog signal. Further, each analog signal is multiplied by the local oscillation signal input from the local oscillator 815 by the mixers 816-1 to 816 -N _BS-Ant , and up-converted to a radio frequency signal. Here, since the upconverted signal includes the signal in the region outside the band of the channel to be transmitted, the filter 815-1 to 817-N _BS-Ant removes the out _- of-band component and transmits the electricity to be transmitted. Generate a dynamic signal. The generated signal is amplified by the high-power amplifier _{818-1~818-N BS-Ant,} and transmitted from the antenna elements _{819-1~819-N BS-Ant.}

In FIG. 6, after the addition synthesis of the signal of each subcarrier is performed by the addition synthesis circuit 812-1 to 812-N _BS-Ant , the processing such as IFFT processing, guard interval insertion, and waveform shaping is performed. However, even if the transmission signal processing circuit 811-1 to 811-N _SDM performs these processings, the IFFT & GI application circuits 813-1 to 813-N _BS-Ant may be omitted in this position in terms of function allocation. Good. In this case, the rest of the signal processing necessary after transmission weight multiplying in the transmission signal processing circuit _{811-1~811-N SDM} refers IFFT processing, insertion of the guard interval, the process of waveform shaping or the like.

Further, transmission weight to be multiplied by the transmission signal processing circuit _{811-1~811-N SDM} is the time of signal transmission process, is acquired from the multi-user MIMO transmission weight calculating circuit 833 provided in the transmission weight processing unit 830. In the transmission weight processing unit 830, the channel information acquisition circuit 831 separately acquires the channel information acquired by the reception unit 85 via the communication control circuit 820, and updates the channel information in the channel information storage circuit 832 while sequentially updating it. Remember. At the time of signal transmission, according to the instruction from communication control circuit 820, multi-user MIMO transmission weight calculation circuit 833 reads channel information corresponding to the destination terminal station apparatus from channel information storage circuit 832, based on the read channel information. The transmission weight corresponding to the combination of the destination station apparatus is calculated. Multi-user MIMO transmission weight calculation circuit 833 outputs the calculated transmission weights to transmission signal processing circuits 811-1 to 811-N _SDM .

  Further, the communication control circuit 820 manages control related to the entire communication, such as management of a terminal station apparatus as a destination and overall timing control. The communication control circuit 820 outputs information indicating a terminal station apparatus or the like as a destination to the transmission weight processing unit 830 that performs signal processing related to the calculation of the transmission weight described above.

(Circuit configuration of the receiving unit 85)
FIG. 7 is a schematic block diagram showing an example of the configuration of the receiving unit 85 in the base station apparatus 80 in a multi-user MIMO system. As shown in FIG. 7, the receiving unit 85 includes antenna elements 851-1 to 851-N _BS-Ant , low noise amplifiers (LNA) 852-1 to 852-N _BS-Ant , a local oscillator 853 and a mixer 854. -1 to 854-N _BS-Ant , filters 855-1 to 855-N _BS-Ant , A / D (analog / digital) converters 856-1 to 856-N _BS-Ant , FFT (Fast Fourier) Transform (Fast Fourier Transform) circuits 857-1 to 857-N _BS-Ant , received signal processing circuits 858-1 to 858-N _SDM, and a reception weight processing unit 860. The reception signal processing circuits 858-1 to 858 -N _SDM and the reception weight processing unit 860 are connected to the communication control circuit 820 shown in FIG. 5. The reception weight processing unit 860 includes a channel information estimation circuit 861 and a multiuser MIMO (MU-MIMO) reception weight calculation circuit 862.

Signals received by antenna elements _{851-1~851-N BS-Ant} is amplified by the low noise amplifier _{852-1~852-N BS-Ant.} The amplified signal and the local oscillation signal output from local oscillator 853 are multiplied by mixers 854-1 to 854-N _BS-Ant , and the amplified signal is down converted from a radio frequency signal to a baseband signal. Ru. Since the downconverted signal includes the signal also in the region outside the frequency band to be received, the filters 855-1 to 855-N _BS-Ant remove out _- of-band components. The signal from which the out-of-band component has been removed is converted into a digital baseband signal by A / D converters 856-1 to 856 -N _BS-Ant . The digital baseband signals are all input to the FFT circuits 857-1 to 857-N _BS-Ant, and the signals on the time axis are taken along the frequency axis at predetermined symbol timings determined by the timing detection circuit which is not described here. It is converted into the above signal (separated into the signal of each subcarrier). The signals separated into the respective subcarriers are input to the reception signal processing circuits 858-1 to 858 -N _SDM and are also input to the channel information estimation circuit 861.

The channel information estimation circuit 861 includes an antenna element of each terminal station apparatus based on a known signal for channel estimation (such as a preamble signal added to the beginning of a radio packet) separated into each subcarrier, and a base station apparatus 80. The channel information between each antenna element 851-1 to 851-N _BS-Ant is estimated for each subcarrier, and the estimation result is output to multiuser MIMO reception weight calculation circuit 862. Multi-user MIMO reception weight calculation circuit 862 calculates reception weight for each subcarrier based on the input channel information. At this time, the reception weights for combining the signals received by the respective antenna elements 851-1 to 851-N _BS-Ant differ for each signal sequence, and the reception signal processing circuit 858-1 corresponding to the signal sequence to be extracted 858-N _SDM is input to each.

Reception signal processing circuits 858-1 to 858 -N _SDM are input from multi-user MIMO reception weight calculation circuit 862 for the signal for each subcarrier input from FFT circuits 857-1 to 857 -N _BS -Ant. The reception weights are multiplied, and the signals received by the respective antenna elements 851-1 to 851-N _BS-Ant are added and synthesized for each subcarrier. The reception signal processing circuits 858-1 to 858 -N _SDM perform demodulation processing on the added and synthesized signal, and output the reproduced data to the MAC layer processing circuit 88. In this demodulation processing, for example, soft decision of the received signal may be performed once, deinterleave processing may be performed as necessary, and error correction processing may be performed thereafter to perform final signal detection.

Here, in different received signal processing circuits 858-1 to 858 -N _SDM , signal processing of different signal sequences is performed. In addition, the MAC layer processing circuit 88 performs processing related to the MAC layer (for example, conversion between data input to and output from the interface circuit 87 and data transmitted and received on a wireless channel, termination of header information of the MAC layer, etc. Do. In this process, the scheduling process circuit 881 performs various scheduling processes including a combination of terminal stations that perform space multiplexing simultaneously in multi-user MIMO transmission, and outputs the scheduling result to the communication control circuit 820. The received data processed by the MAC layer processing circuit 88 is output to an external device or network via the interface circuit 87.

  Further, the communication control circuit 820 manages control related to the entire communication, such as management of the terminal station apparatus of the transmission source and overall timing control. Further, information indicating the terminal station apparatus or the like of the transmission source is input from the communication control circuit 820 to the reception weight processing unit 860 that performs signal processing related to the above-described calculation of the reception weight.

As for signal reception, as in the case of transmission, in the wideband system using the OFDM modulation method or SC-FDE method, the multiplication of the above-mentioned reception weight is performed for each subcarrier. That is, for the signals output from A / D converters 856-1 to 856-N _BS-Ant , FFT circuits 857-1 to 857-N _BS-Ant perform FFT to separate into subcarriers, and the sub Signal processing in channel information estimation circuit 861 and received signal processing in received signal processing circuits 858-1 to 858-N _SDM are performed for each carrier.

The above is the description of the configurations of the base station apparatus 80, the transmitter 81, and the receiver 85 in the multiuser MIMO system. As described above, for example considers the transmission signal processing circuit 811-1～N _SDM and the reception signal processing circuit 858-1～N _SDM respectively a signal processing circuit for the signal sequence of _{N SDM} systems of single terminal station device, further If the multi-user MIMO transmission weight calculation circuit 833 and the multi-user MIMO reception weight calculation circuit 862 are regarded as transmission / reception weight calculation circuits for single-user MIMO, the base station apparatus 80 and transmission in the single-user MIMO system are basically described above. The configuration of the unit 81 and the receiving unit 85 is shown.

The important point here is that the local oscillator 815 in the transmission unit 81 is shared by the mixers 816-1 to 816 -N _BS-Ant in each antenna system of the transmission unit 81, the local oscillator 853 in the reception unit 85 is a reception unit The mixers 854-1 to 854-N _BS-Ant in each of the 85 antenna systems are common points. Although the phases of the transmit and receive signals are adjusted by each antenna, the phase relationship of the signals input from the respective local oscillator 815 or the local oscillator 853 is always constant, so that transmission and reception can be performed in any phase relationship. It can be determined whether the weight should be multiplied. When the local oscillator uses a plurality of asynchronous ones in the transmitter 81 or in the receiver 85, at least the transmitter 81 does not effectively function as a directivity control that multiplies transmission weights. Care should be taken in this regard in the design of the device.

[Features of Line-of-sight Dominant MIMO Channel]
First, the spatial multiplexing characteristics in the propagation path in which the sight wave is dominant are organized. The channel matrix when the transmitting station and the receiving station are in the line-of-sight environment is H _LOS , and the channel matrix in which each component of the matrix is independent and uncorrelated is H _{i. i. d} . For simplicity, the H _LOS is substituted by a matrix in which each component is all “1”, and the following channel matrix is used for 16 transmitting antennas, 16 receiving antennas, 256 transmitting antennas, and 16 receiving antennas. For one case, the distribution of the absolute values of the 16 singular values of the channel matrix given by the following equation (9) is evaluated.

FIG. 8 shows the distribution characteristic of the absolute value of the singular value for each channel matrix. FIG. 8 (a) shows the result of _{Hi. i. In} the case of _d. only (iid channel), FIG. 8 (b) shows the distribution characteristic of the absolute value of the singular value in the case of the Rice channel (Rician channel) expressed by the equation (9) Show. In each of FIG. 8A and FIG. 8B, the distribution characteristic on the left side is the distribution characteristic when 16 transmitting and receiving antenna elements are used, and the distribution characteristic on the right side is 256 transmitting antenna elements. Distribution characteristics when the When the number of transmitting and receiving antenna elements is equal to 16 as well, the distribution of the absolute values of the singular values tends to widen, and the gap between the absolute values of the first singular value and the sixteenth singular values tends to widen. However, when the number of transmitting or receiving antennas becomes redundant, for example, 256 transmitting antenna elements, the absolute value of the singular value is H _{i. i.} There is almost no difference between the distribution probability 0% and the 100% value without being influenced by the value of the random number for each evaluation of _d . This is common to FIGS. 8 (a) and 8 (b) _{. i. In} the case of _d. only, the gap from the first singular value to the sixteenth singular value becomes very small while in the case of the rice channel of FIG. 8 (b), the first singular value and the second singular value The gap between the absolute values of is 20 dB, which is 10 dB greater than the Rice coefficient, while the gap between the second singular value and the sixteenth singular value is small. That is, it can be understood from FIGS. 8 (a) and 8 (b) that the top of FIG. 2 (c) corresponds to the first singular value even if the number of antenna elements is increased when the line-of-sight wave is dominant. The line gain concentrates too much on the transmission line corresponding to the pipe of (λ ₁ ), and the second (λ ₂ ) and third (λ ₃ ) pipes from the top of FIG. It means that the corresponding transmission line can hardly be used.

  On the other hand, when using a millimeter wave or the like, the free space propagation loss increases depending on the frequency, so for example, a gain of about 24 dB must be obtained somewhere at 80 GHz for 5 GHz. For this purpose, it is effective to increase the size of the antenna, but it is necessary to carry out the increase in size of the antenna for spatial multiplexing and the increase in size of the antenna for gaining line gain from different viewpoints .

Atsushi Ota, Atsushi Kurosaki, Ikki Maruta, Takuto Arai, Masataka Iizuka, "B-5-175 Proposal of a large-scale antenna wireless entrance system", Proceedings of the IEICE General Conference 2013-Communications (1), 2013 March 5, p. 585 Takuto Arai, Atsushi Ota, Atsushi Kurosaki, Itsuki Maruta, Masataka Iizuka, "B-5-176 Large-scale Antenna Wireless Entrance System Transmission / reception weight calculation method," Proceedings of the 2013 IEICE General Conference ), March 5, 2013, p. 586 Kazuki Maruta, Atsushi Ota, Atsushi Kurosaki, Takuto Arai, Masataka Iizuka, "B-5-177 Interference Suppression among Users in Large-scale Antenna Wireless Entrance System", Proceedings of the 2013 IEICE General Conference 1), March 5, 2013, p. 587 Ryo Kurosaki, Atsushi Ota, Ikki Maruta, Takuto Arai, Masataka Iizuka, "B-5-178 Low Correlation Scheduling Method for Large-scale Antenna Wireless Entrance Systems", Proceedings of the 2013 IEICE General Conference ), March 5, 2013, p. 588 Akinori Ohara, Atsushi Suyama, Shin Kiyun, Yukihiko Okumura, "Combined processing of fixed beamforming and eigenmode precoding in ultra-fast Massive MIMO transmission using RCS 2013-349 high frequency band", IEICE Technical Report, Wireless Communication System (RCS), Vol. 113, no. 456, February 24, 2014, p. 259-p. 264

  As an environment where it is required to increase the capacity of the transmission path in the mobile network in the future, (Environment 1) In the access system to mobile users, large capacity transmission from the base station apparatus to the terminal station apparatus of the mobile user, (Environment 2) Small When installing a cell radio base station apparatus, for example, on a wall of a building, mass communication at a radio entrance that wirelessizes the entrance line to the base station apparatus for construction reasons, (environment 3) A large capacity transmission of a wireless entrance as an entrance line may be considered, for example, which aggregates data of a large number of mobile users once in a train and collectively transfers the collected data to a ground network.

  In the case of (environment 1), for the purpose of efficient transmission to users present in a relatively narrow area, a service area is formed in a direction looking down from a high place such as a wall or roof of a building, In the station apparatus, the line-of-sight environment is generally secured from the physical characteristics that radio waves from above reach, and the antenna element mounted by the terminal station apparatus also has some directivity considering the arrival of radio waves from above If an antenna with gain is used, the line of sight results in a very dominant environment. Similarly, with regard to (environment 2) to (environment 4), an environment in which a sight wave is dominant is assumed and a problem, but in the present specification, attention is focused on (environment 1) in particular.

  Here, as described above, in general, in spatial multiplexing transmission using a MIMO channel matrix, a multi-path environment in which a large number of reflected waves exist is effective, and so suitable when the direct line-of-sight component is dominant. It is not known that. In order to avoid this problem and perform high-order spatial multiplexing transmission in an environment in which line of sight waves dominate, it is necessary to make the antenna elements of the base station apparatus spatially large (expand the antenna aperture length). It is one choice. That is, it is possible to approach the multipath environment in a pseudo manner by forming a situation where the path lengths on the transmission path between the antenna elements are randomly different.

  On the other hand, as mentioned above, in the future mobile networks are required to increase the capacity of transmission paths, and considering the operation with a wide frequency bandwidth, operation in high frequency bands such as quasi-millimeter wave and millimeter wave Is forced. The point to be noted here is that when a high frequency band is used, each device or between the device and the antenna is connected by a coaxial cable etc., and when transmitting and receiving signals etc. are transmitted on this cable, transmission on the cable The problem is that the loss is very large. Specifically, although a 60 GHz band signal or the like depends on the cable, a loss of about 15 dB is expected per 1 m.

  Even if a large number of antennas are installed to secure the line gain while using the millimeter wave band which is disadvantageous as a gain in line design, even if a large number of cables are connected between spatial spreads of the antennas It does not make sense if a cable loss occurs. Furthermore, when the number of antenna elements is increased in order to secure the line gain, a huge number of cables will be distributed between the spatial spread of the antenna, and the transmission loss between If low-loss cables are used to reduce the cable routing between them, the installation freedom such as bending of the cables is also low, and the restriction on the installation of the base station equipment becomes very large and impractical.

  That is, in the future, in an access system in a mobile network, although high-speed waves such as millimeter waves are used to realize large-capacity transmission by high-order spatial multiplexing, even in the environment where line-of-sight waves are dominant It is necessary to solve the problem of the above and build a wireless system.

In view of the above circumstances, the present invention provides a terminal station apparatus capable of increasing transmission capacity in a radio communication system performing MIMO transmission in a communication environment in which a sight wave is dominant, a terminal station control method and a terminal station apparatus The purpose is to provide a manufacturing method.

  One embodiment of the present invention is a terminal station apparatus in a wireless communication system comprising a base station apparatus comprising a plurality of first antenna elements and at least one terminal station apparatus, wherein It is a terminal station apparatus provided with the antenna board | substrate by which it was movably attached, and several 2nd antenna elements arrange | positioned at the main surface of the said antenna board | substrate.

  Further, according to one aspect of the present invention, in the terminal station apparatus described above, the antenna substrate is a rectangular plate having a certain thickness, and one side of the antenna substrate is hinged to the housing. Attached, the antenna substrate rotates about the hinge portion.

  Further, according to one aspect of the present invention, in the terminal station apparatus, the antenna substrate is a rectangular plate having a certain thickness, and the antenna substrate is provided via a guide portion provided in the housing. The guide portion guides the moving direction of the antenna substrate to be parallel to the main surface of the housing.

  Further, according to one aspect of the present invention, in the terminal station apparatus described above, the antenna substrate is a fan-shaped plate having a certain thickness, and the antenna substrate is attached in the vicinity of the main portion of the fan shape. The antenna substrate is attached to the housing via a hinge, and the antenna substrate rotates about the hinge.

  Further, according to one aspect of the present invention, in the terminal station apparatus described above, the antenna substrate is an elongated rectangular plate having a certain thickness, and one end of the antenna substrate has a hinge portion on the housing. And the antenna substrate is rotated about the hinge portion.

  Further, according to one aspect of the present invention, in the terminal station apparatus described above, the signal processing section further performs signal processing of wireless communication with the base station apparatus, and the signal processing section further includes the first antenna element and the signal processing section. At least one of a transmission weight vector and a reception weight vector for a MIMO channel matrix used for wireless communication with a second antenna element is a first right singular vector and a first left corresponding to a first singular value of the MIMO channel matrix. It is calculated based on at least one of the singular vectors or at least one of the approximate solution of the first right singular vector and the approximate solution of the first left singular vector, and independent using the calculated transmit weight vector or receive weight vector. Space multiplex transmission of signal sequences.

  Further, one aspect of the present invention is a method of manufacturing a terminal station apparatus performing wireless communication with a base station apparatus provided with a plurality of first antenna elements, wherein an antenna substrate is moved with respect to a housing of the terminal station apparatus. It is a manufacturing method of the terminal | end station apparatus which has the 1st step of possible installation, and the 2nd step of arrange | positioning a several 2nd antenna element on the main surface of the said antenna board | substrate.

  According to the present invention, it is possible to increase the transmission capacity in a wireless communication system that performs MIMO transmission in a communication environment in which a sight wave is dominant.

FIG. 1 shows an overview of an example of MIMO transmission. It is a conceptual diagram of the example of eigenmode transmission. FIG. 1 shows an overview of an example of a large scale antenna system. It is a figure showing the example of the impulse response in line-of-sight environment and non-line-of-sight environment. It is a schematic block diagram which shows an example of a structure of the base station apparatus in a multiuser MIMO system. It is a schematic block diagram which shows an example of a structure of the transmission part in the base station apparatus in a multiuser MIMO system. It is a schematic block diagram which shows an example of a structure of the receiving part in the base station apparatus in a multiuser MIMO system. It is a figure which shows the example of the distribution characteristic of the absolute value of the singular value for every channel matrix. It is a figure which shows the example of the linear array by which 100 antenna elements of a base station apparatus are arrange | positioned at equal intervals. It is a figure which shows the example of the linear array by which 100 antenna elements of a base station apparatus were divided into 4 groups of every 25 and arrange | positioned. It is a schematic block diagram which shows an example of a structure of the base station apparatus in the MIMO system in related technology of this invention. It is a schematic block diagram which shows an example of a structure of the 1st transmission signal processing part in the base station apparatus of the related technology of this invention. It is a schematic block diagram which shows an example of a structure of the 1st reception signal processing part in the base station apparatus of the related technology of this invention. It is a schematic block diagram which shows an example of a structure of the terminal | end station apparatus in the related technology of this invention. It is a schematic block diagram which shows an example of a structure of the transmission part in the terminal | end station apparatus in the related technology of this invention. It is a schematic block diagram which shows an example of a structure of the receiving part in the terminal | end station apparatus in the related technology of this invention. It is a figure which shows an example of another structure of the receiving part in the terminal | end station apparatus in the related technology of this invention. It is a figure which shows the example of the apparatus structure in the 2nd received signal processing part of a base station apparatus thru | or the 2nd received signal processing circuit of a terminal | end station apparatus. It is a figure which shows the example of a different structure of the transmission part of the terminal | end station apparatus in the related technology of this invention. It is a flowchart which shows the signal processing at the time of the signal transmission in related technology of this invention. It is a flowchart which shows the 1st example of the signal processing flow at the time of the signal reception in related technology of this invention. It is a flowchart which shows the outline | summary of the 2nd example of the signal processing flow at the time of the signal reception in related technology of this invention. It is a figure which shows the case where a base station apparatus is equipped with four parabola antennas, and a terminal station apparatus is equipped with 16 linear antenna-like antenna elements. It is a figure which shows the example of the path | route difference for every antenna element by the side of the terminal | end station apparatus from the parabola antenna by the side of a base station apparatus. It is a figure which shows the 2nd example of the case where four parabola antennas were mounted in the base station apparatus, and 16 antenna elements were mounted in linear array shape at the terminal | end station apparatus. It is a figure which shows the example of the antenna arrangement | sequence mounted in the terminal | end station apparatus in the related technology of this invention. It is a figure which shows the form in case a user holds a terminal | end station apparatus in hand, and uses it. FIG. 16 is a diagram showing a case where a first signal processing unit of a base station apparatus is linearly disposed at a high place such as a building wall surface in the related art of the present invention. It is a figure which shows the relationship of the arrangement | sequence of the antenna element of a terminal | end station apparatus, and the arrangement | sequence of a 1st signal processing part. It is a figure which shows the structural example of the terminal | end station apparatus in 1st Embodiment concerning this invention. It is a figure which shows the structural example of the terminal | end station apparatus in 2nd Embodiment which concerns on this invention. It is a figure which shows the structural example of the terminal | end station apparatus in 3rd Embodiment which concerns on this invention. It is a figure which shows the structural example of the terminal | end station apparatus in 4th Embodiment concerning this invention. It is a figure which shows the relationship between the direction of the linear array antenna of a terminal | end station apparatus, and the arrangement | sequence of the 1st signal processing part of a base station apparatus.

Embodiments of the present invention will be described in detail with reference to the drawings.
Here, symbols and variables used in the following description will be described.
N _SDM : Space multiplexing number.
N, M, N ', M': natural numbers.
i, j, m, n: Mainly serial numbers of antenna elements etc. (general integers).
k: Subcarrier number (frequency component number).
N _BS-Ant : The total number of antenna elements of the base station apparatus.
_N'BS-Ant : The number of antenna elements provided in the first transmission signal processing unit or the first reception signal processing unit of the base station apparatus.
N _MT-Ant : Number of antenna elements of the terminal station apparatus.
N _Ant : Number of antenna elements of the base station apparatus or terminal station apparatus.
N _SC : Number of subcarriers.
N _FFT : Number of points of FFT.
L: Distance.
K: Rice coefficient.
λ _k : wavelength of the k-th subcarrier.
r _ji : Distance between the ith antenna element on the transmitting side and the jth antenna element on the receiving side.
h _ji , h ' _ji : Channel information between the i-th antenna element on the transmitting side and the j-th antenna element on the receiving side (because it has frequency dependency, it is the k-th frequency component if necessary in the description In some cases, this is explicitly stated.
d: distance between antenna elements.
Δd _mn : distance between the n-th antenna element and the m-th antenna element.
ΔL _m : Path length difference of the m-th antenna element based on the first antenna element.
c: speed of light (3 × 10 ⁸ m / s).
f _c : Center frequency of wireless signal [Hz].
f _k : frequency [Hz] of the k th subcarrier of the baseband signal.
t: Time.
W: Bandwidth [Hz].
Δt: Sampling period (Δt = 1 / W).
ψ _j (t), Φ _j (t): Received signal (sampled value) at the j-th antenna element at time t.
φ _j ^(k) (t): A received signal of the kth subcarrier at the jth antenna element at time t (a value focused on a predetermined subcarrier in the sampling value).
η _k : Offset value of the k-th subcarrier in consideration of the complex phase of 2π period when using the least squares method.
u _m : m th left singular vector.
v _m : m th right singular vector.

First, prior to describing the embodiments of the present invention, techniques related to the present invention (hereinafter, referred to as related techniques) will be described.
[Space multiplexing transmission using virtual transmission paths corresponding to a plurality of first singular values]
(Summary of basic principles)
As described in FIG. 8 as well, in the environment where the line-of-sight wave is dominant as shown in FIG. 8B, the gap between the absolute values of the first singular value and the second singular value becomes large, and the second singularity When a transmission path corresponding to a singular value greater than the value is used, Hi _{. i.} Communication will be performed with a slight line gain gained using the components of _d . However, for example, in the case of irradiating the area of the limited small cell below from the base station apparatus installed on the wall of the building, the base station apparatus side mounts an antenna with high directivity gain. Furthermore, in a situation where it is expected that a small antenna element capable of obtaining a directional gain by utilizing features such as a short wavelength millimeter wave is expected to be mounted on the terminal station side, the transmitting side and the receiving side The multipath component is expected to be very limited as compared to a microwave band system or the like in which both mount omnidirectional antennas. Therefore, the characteristics of the MIMO transmission in the case where only the line of sight wave is considered are organized.

FIG. 9 is a diagram showing an example of a linear array in which 100 antenna elements of a base station apparatus are arranged at equal intervals. In FIG. 9, reference numeral 40 denotes a wireless communication system, reference numeral 301 denotes a base station apparatus, and reference numeral 302 denotes a terminal station apparatus. In FIG. 9, the 100 antenna elements of the base station apparatus 301 are mounted in a linear array. 100 antenna elements of the base station apparatus 301 is arranged at regular intervals over the length D _1. Further, 16 of the antenna element of the terminal station device 302 is equally spaced linear array shape over the length D _2.

FIG. 10 is a diagram showing an example of a linear array in which 100 antenna elements of the base station apparatus are divided into four groups of 25 each. In FIG. 10, reference numeral 50 is a wireless communication system, reference numeral 303 is a base station apparatus, reference numeral 302 is a terminal station apparatus, reference numerals 304-1 to 304-4 are first signal processing units, and reference numeral 305 is a second signal. A processing unit (strictly, it includes other base station apparatus functions such as an interface circuit, a MAC layer processing circuit, and a communication control circuit). In FIG. 10, the 100 antenna elements of the base station apparatus 303 are divided into four groups of 25 antenna elements. 25 antenna elements in the same group, in a very narrow interval as compared with the case of FIG. 9, over a short length D ₃ than the length D _1, are arranged in a linear array form.

In FIG. 10, 100 antenna elements of the base station apparatus 303 are mounted in a linear array for each group (25 antenna elements). That is, the 100 antenna elements of the base station apparatus 303 are mounted in a linear array for each of the first signal processing units 304. The first signal processing units 304-1 to 304-4 form one directional beam for each group (25 antenna elements) by signal processing. Further, 16 of the antenna element of the terminal station device 302 is equally spaced linear array shape over the length D _2.

  Here, in each of the two cases shown in FIG. 9 and FIG. 10, transmission characteristics in the case of transmitting four signal systems by space multiplexing (four multiplexing) are compared. The characteristics of the transmission can be grasped by the gain of each transmission line shown in FIG. 2C, which corresponds to the square of the absolute value of the singular value obtained by the singular value decomposition of the channel matrix. In the case shown in FIG. 9, assuming, for example, downlink, if the base station apparatus 301 is the transmitting station 11 and the terminal station apparatus 302 is the receiving station 12, the size of the channel matrix is 16 × 100. Perform singular value decomposition on this matrix.

On the other hand, in the case shown in FIG. 10, the following procedure is assumed to grasp its characteristics. First, the base station apparatus 303 is a 16 × 25 channel matrix formed by 25 antenna elements of each group of the base station apparatus 303 and 16 antenna elements of the terminal station apparatus 302 (in the case of downlink) It is assumed that singular value decomposition is performed on the basis of, and transmission is performed using the first right singular vector. Specifically, the base station device 303 is a portion between each of 25 antenna elements connected to the first signal processing units 304-1 to 304-4 and 16 antenna elements of the terminal station device 302. singular value decomposition of the channel matrix _H 1 to H _4. The partial channel matrices H _{1 to} H ₄ are shown in equation (10).

Each partial channel matrix H _{1 to} H ₄ is a 16 × 25 matrix. Therefore, v _ij forming each right singular vector is a 25-dimensional vector, and represents the right singular vector corresponding to the j-th singular value in the i-th group of four antenna groups. Similarly, u _ij forming each left singular vector is a 16-dimensional vector, and represents the left singular vector corresponding to the j-th singular value in the i-th group of the four antenna groups, where An overall channel matrix between all the antenna elements of the base station apparatus 303 and the terminal station apparatus 302 is shown in equation (11).

The transmission weight matrix W _Tx here is shown in equation (12).

Equation (12), the notational convenience, but using the Hermitian conjugate representation of the transmission weight matrix W _Tx, the size of the transmit weight matrix W _Tx itself is 100 × 4. As a result, the product of the entire channel matrix and the transmission weight matrix is shown in equation (13).

Here, H _i v _i1 is a 16 × 1 matrix (column vector), which matches λ _i u _{i1 according} to equation (10). As a result, the overall size of the product of the entire channel matrix and the transmission weight matrix is 16 × 4. In general, since the first left singular vectors of the partial channel matrices H _{1 to} H ₄ are not orthogonal to each other, reception weights for signal separation are formed and multiplied at the time of reception. However, when the first left singular vectors of the partial channel matrices H _{1 to} H ₄ are in an environment substantially orthogonal to each other, the matrix represented by the product of the entire channel matrix and the transmission weight matrix is subjected to singular value decomposition The square value of the absolute values of the four singular values approximately matches the channel gain of the transmission line of FIG. 2 (c). In the evaluation here, it is assumed that each element of the channel matrix is expressed by the following equation (14) by the free space propagation model in which only the line of sight wave is considered.

Here, r _ij represents the distance between the i-th antenna on the transmitting side and the j-th antenna on the receiving side, and λ represents the wavelength. In order to grasp the entire feature, the coefficients to be multiplied by the coefficients as a whole are omitted here for the sake of simplification.

_{Therefore, L = 100m, D 1 =} 12m, D 2 = 10cm in FIG _10, D 3 = _30cm, for the case of frequency 80 GHz, and compares the characteristics of Fig. 9 which is installed in a comparable antenna aperture length. Here, assuming that the absolute value of the singular value is X as the channel gain, the channel gain is evaluated as 20 Log (X) [dB]. At this time, while the gains of the four lines in FIG. 9 are respectively -56.5 dB, -83.4 dB, -118.3 dB and -157.2 dB, the above-described processing is applied to FIG. Are respectively -62.5 dB. In the case of FIG. 9, only the line with the largest gain corresponding to the first singular value of FIG. 2 (c) has a large value, and the gain of the line corresponding to the remaining singular values is relatively small. Although dependent also on the value of a parameter such as antenna gain, it is in a situation where only the line corresponding to the first singular value can be used. On the other hand, in the case of FIG. 10, it can be seen that four transmission paths can be used almost equally. Here, although the gain difference with respect to the first singular value in FIG. 9 and the gain difference with respect to the singular value in FIG. 10 is 6 dB, the number of antenna elements used for directional beam forming is 1/100 to 25 in FIG. It corresponds to 4 and its corresponding 10 Log (1/4) =-6 dB. In other words, although the efficiency is reduced to 1⁄4 by dividing the antenna element group into four, it is better to multiplex four signal sequences to the channel capacity due to the Shannon limit than to improve the SNR by 6 dB. It is overwhelmingly efficient in terms of growth.

  If the received signal power of the reflected wave component is strong enough that the line gain of the line corresponding to the singular value after the second singular value can be effectively used by setting the values of parameters such as transmission power and antenna gain Generally, if the number of antenna elements is increased to compensate for the decrease in line gain due to the use of high frequency bands such as millimeter waves, the line gain of the line corresponding to the singular value after the second singular value is sufficient. In general, it is difficult to think about the situation where there is a problem, and the transmission capacity is increased in the case of FIG. 10 in which transmission for four lines is performed in parallel compared to the case of FIG. It can be viewed as being suitable for It is effective to group antennas in this manner and efficiently use virtual transmission paths corresponding to the first singular value in each group.

(About the circuit configuration of the base station apparatus in the related art of the present invention)
FIG. 11 is a schematic block diagram showing an example of the configuration of base station apparatus 70 in the MIMO system in the related art of the present invention. Although FIG. 10 illustrates the case of point-to-point type one-to-one communication with one base station apparatus 303 and one terminal station apparatus 302, it goes without saying that there are a plurality of terminal station apparatuses 302. It does not matter. Transmission and reception of the signals in FIG. 10 are simultaneously communicated with only one terminal station apparatus 302 at the same time in terms of a focused subcarrier, and in the form of single-user MIMO transmission, the communication target is one terminal station apparatus 302 by scheduling. Is selected. If OFDMA is used in access control, different terminal station apparatuses 302 may be allocated to each subcarrier, but if attention is paid to each subcarrier, the allocation is limited to one terminal station apparatus 302. Further, in the following description, although a wideband system is assumed to simplify the explanation, signal processing for each subcarrier on the frequency axis such as OFDM or SC-FDE will be described, but other systems will be described. It can also be extended (for example, a narrow band single carrier system).

  As shown in FIG. 11, the base station device 70 corresponding to the base station device 303 includes first transmission signal processing units 181-1 to 181-4, a second transmission signal processing unit 71, and first reception. The signal processing units 185-1 to 185-4, the second received signal processing unit 75, the interface circuit 77, the MAC (Medium Access Control) layer processing circuit 78, and the communication control circuit 120 are provided. The MAC layer processing circuit 78 has a scheduling processing circuit 781.

  The base station device 70 inputs and outputs data with an external device or a network via the interface circuit 77. The interface circuit 77 detects data to be transferred on the wireless channel among the input data, and outputs the detected data to the MAC layer processing circuit 78. The MAC layer processing circuit 78 performs processing related to the MAC layer in accordance with an instruction of the communication control circuit 120 that performs management control of the entire operation of the base station device 70. Here, the processing related to the MAC layer includes conversion of data input / output by the interface circuit 77, data transmitted / received on the wireless channel, addition of header information of the MAC layer, and the like. In this process, the scheduling process circuit 781 performs various scheduling processes of the terminal station apparatus 302 that performs space multiplexing. The scheduling processing circuit 781 outputs the scheduling result to the communication control circuit 120. In MIMO transmission, since signals of a plurality of signal sequences are spatially multiplexed and transmitted at one time, signal sequences of a plurality of systems are output from the MAC layer processing circuit 78 to the second transmission signal processing unit 71.

  Although the operation of the second transmission signal processing unit 71 will be described later, basically, predetermined modulation processing is performed on a plurality of series of signals from the MAC layer processing circuit 78, and if necessary, some precoding processing (on the transmission side Equalization processing, signal separation processing, and the like), and the like, and output to the first transmission signal processing units 181-1 to 181-4. At this time, regardless of using OFDM or SC-FDE, when performing signal processing on the frequency axis by the first transmission signal processing units 181-1 to 181-4, the second transmission signal processing unit A signal on the frequency axis is generated in 71 and output to the first transmission signal processing units 181-1 to 181-4. When the first transmission signal processing unit performs signal processing on the time axis, a signal on the time axis may be output. A plurality of antenna elements are connected to each of the first transmission signal processing units 181-1 to 181-4 as shown in FIG. 10, and the transmission signals are output to the respective antennas. At this time, a signal obtained by multiplying the transmission weight vector corresponding to the first singular value among the antenna element groups grouped for each of the first transmission signal processing units 181-1 to 181-4 (strictly, For example, in the case of OFDM, a signal obtained by combining signals of respective subcarriers is converted into a time axis component, and a signal obtained by up-converting the signal into a radio frequency is transmitted from each antenna.

  Next, at the time of reception, the signals received by the plurality of antenna elements connected to the first received signal processing units 185-1 to 185-4 (precisely, the received radio frequency signals are reduced to baseband signals) For example, in the case of OFDM, this time-axis signal is converted to a frequency-axis signal by FFT), multiplied by a predetermined reception weight vector, converted into one complex scalar quantity for each subcarrier, and The received signal processing unit 75 outputs the received signal. The second received signal processing unit 75 refers to four received signal sequences in this example, and first performs channel estimation for each subcarrier using a known training signal given at the beginning of the received signal, A × 4 MIMO channel matrix is obtained for each subcarrier. The reception weight matrix is calculated based on this channel matrix, and the detection processing of the signal transmitted based on the acquired reception weight matrix is performed. For example, an inverse matrix of ZF (Zero Forcing) type is used, or a reception weight matrix of Maximum Mean Square Error (MMSE) type is used. If there is enough time for signal processing, MLD (Maximum Likelihood Detection) or simplified MLD (QR-MLD) using QR decomposition may be used. The signal detected by this reception signal processing is output to the MAC layer processing circuit 78, is subjected to processing of a predetermined MAC layer, and is output to the network side through the interface circuit 77.

FIG. 12 is a schematic block diagram showing an example of a configuration of first transmission signal processing section 181 in base station apparatus 70 according to the related art of the present invention. As shown in FIG. 12, the first transmission signal processing unit 181 includes a first transmission signal processing circuit 111 and an IFFT (Inverse Fast Fourier Transform) & GI (Guard Interval) guard circuit 813. -1 to 813-N ' _BS-Ant , D / A (digital / analog) converter 814-1 to 814- (N' _BS-Ant ), local oscillator 815, and mixers 816-1 to 816- N'BS _-Ant ), filters 817-1 to 817- (N'BS _-Ant ), high power amplifiers (HPA) 818-1 to 818- (N'BS _-Ant ), antenna element 819-1 Through 819- (N ' _BS -Ant) and the first transmission weight processing unit 130. _N'BS-Ant is a value obtained by dividing the total number of antenna elements of the base station apparatus 70 by the number of space multiplexing (= _NBS-Ant / _NSDM ). In short, N ′ _{BS -Ant} represents the number of antenna elements included in one first transmission signal processing unit 181. The first transmission signal processing circuit 111 is connected to the second transmission signal processing unit 71 shown in FIG. Further, the first transmission signal processing circuit 111 and the first transmission weight processing unit 130 are connected to the communication control circuit 120 via the second transmission signal processing unit 71 shown in FIG. In the example of FIG. 11, although the base station apparatus 70 is provided with four 1st transmission signal processing parts (181-1 to 181-4), the description will be given focusing on one of them.

The first transmission weight processing unit 130 includes a first channel information acquisition circuit 131, a first channel information storage circuit 132, and a first transmission weight calculation circuit 133. Here, IFFT & GI imparting circuit 813-1~813- (N _'BS-Ant) from the antenna element 819-1~819- (N' _BS-Ant) of the circuit to the subscript (N _'BS-Ant) is Represents the number of antenna elements provided in the first transmission signal processing unit 181 of the base station device 70.

In the related art of the present invention, since signals of a plurality of systems N _SDM (= 4) are spatially multiplexed and transmitted to one terminal station apparatus 302, a plurality of systems of signal sequences transmit from the MAC layer processing circuit 78 to the second transmission. A transmission signal is input to each of the first transmission signal processing units 181-1 to 181-4 via the signal processing unit 71. When the data to be transmitted to the destination terminal station apparatus 302 is input from the MAC layer processing circuit 78, the second transmission signal processing unit 71 generates a radio packet to be transmitted by a radio channel and performs modulation processing. Here, in the case of using, for example, the OFDM modulation scheme, the signal of each signal sequence is modulated for each subcarrier. The signal subjected to the modulation processing is subjected to precoding processing as needed. The precoding processing here may be multiplication of a transmission weight matrix for suppressing leakage of signals between virtual transmission paths corresponding to a plurality of first singular values. Alternatively, such precoding processing may not be performed. The signal of the N _SDM system generated in this manner is input to each of the first transmission signal processing units 181-1 to 181-4.

In each of the first transmission signal processing units 181-1 to 181-4, the input digital baseband signal input #i (i is 1 to N _SDM ) is input to the first transmission signal processing circuit 111-i. Ru. The first transmission signal processing circuit 111 basically performs transmission weight multiplication and signal processing of the remaining physical layer. For example, if the OFDM modulation scheme is used, the first transmission signal processing circuit 111 multiplies the input baseband signal subjected to the modulation processing by the transmission weight for each subcarrier. The signal multiplied by the transmission weight corresponding to each antenna element 819-1 to 819- (N ' _BS-Ant ) is subjected to the remaining signal processing as necessary, and IFFT & GI adding circuits 813-1 to 813- ( At _N'BS-Ant ), the signal on the frequency axis is converted to the signal on the time axis. The converted signal is further subjected to processing such as insertion of guard intervals and waveform shaping between OFDM symbols (between SC-FDE (Single-Carrier Frequency Domain Equalization) block transmission blocks), and the antenna element 819. The digital sampling data is converted to a baseband analog signal by the D / A converter 814-1 to 814- (N'BS _-Ant ) for each of -1- to 819- (N'BS _-Ant ). It will be. Further, each analog signal is multiplied by the local oscillation signal input from the local oscillator 815 by the mixers 816-1 to 816-(N ′ _BS -Ant), and up-converted to a radio frequency signal. Here, since the upconverted signal includes the signal outside the band of the channel to be transmitted, the filters 815-1 to 817- (N'BS _-Ant ) remove the out-of-band signal and transmit it. An electrical signal to be generated is generated. The generated signal is 'is amplified by _(BS-Ant, antenna elements 819-1~819- (N high-power amplifier 818-1~818- N)' is transmitted from the _BS-Ant).

  The transmission weight vector by which the baseband signal is multiplied by the first transmission signal processing circuit 111 is determined by the first transmission weight calculation circuit 133 included in the first transmission weight processing unit 130 at the time of signal transmission processing. It is acquired. In the first transmission weight processing unit 130, the first channel information acquisition circuit 131 transmits the channel information acquired by the first reception signal processing units 185-1 to 185-4 via the communication control circuit 120 (strictly, Is separately acquired by the second reception signal processing unit 75 and the second transmission signal processing unit 71), and is stored in the first channel information storage circuit 132 while being sequentially updated. At the time of signal transmission, the first transmission weight calculation circuit 133 reads channel information corresponding to the destination terminal station apparatus from the first channel information storage circuit 132 according to the instruction from the communication control circuit 120, and the read channel information The transmission weight vector is calculated based on

  There are several variations in the channel estimation method and transmission / reception weight calculation method in the case of utilizing a virtual channel corresponding to the first singular value, and the details of a method for efficiently acquiring this will be described later. As an example, the transmission weight vector may use, for example, a first right singular vector obtained by performing singular value decomposition on the acquired channel matrix.

Alternatively, paying attention to one antenna element at the central portion of the antenna on the terminal station apparatus 302 side, the one antenna element and one of the received signal processing units (one of 185-1 to 185-4) of the base station apparatus 70 Components of the transmission weight vector may be obtained by the equation (7) on the basis of the channel vector between the antenna elements 819-1 to 819-4 and N ′ _BS-Ant provided in All weights may be made constant with respect to the value given by the combination weight) or the equation (7) (weight of equal gain combination).

  Or, when the transmitting side multiplies a plurality of antenna elements by a predetermined transmission weight vector and transmits a signal, although one signal is actually transmitted from a plurality of transmitting antennas, it is effectively one. Since it is equivalent to the one transmitted from the virtual antenna element of the above, a training signal is transmitted from this one virtual antenna element by multiplying a predetermined transmission weight vector, and this one virtual antenna element and each A vector of channel information to and from the receiving antenna may be obtained, and each component of the receiving weight vector may be obtained by equation (7) based on this vector (weight of maximum ratio combining) or by equation (7) It is also possible to make all absolute values constant with respect to a given value (weight of equal gain combination).

  If the channel vector at the time of reception is known, it is possible to obtain uplink channel information by the implicit feedback method, and based on the uplink channel vector determined in this way, the transmission weight vector is obtained. You may calculate similarly. Similarly, based on the uplink reception weight vector, the transmission weight vector may be calculated by an implicit feedback method in which calibration processing is directly performed on the uplink reception weight vector.

  The first transmission weight calculation circuit 133 outputs the transmission weight vector calculated in this manner to the first transmission signal processing circuit 111. Further, the communication control circuit 120 manages control related to the entire communication, such as management of a terminal station apparatus as a destination and overall timing control. The communication control circuit 120 outputs information indicating a terminal station apparatus or the like as a destination to the first transmission weight processing unit 130 that performs signal processing related to the calculation of the transmission weight described above.

  In the above description, the first channel information acquisition circuit 131 acquires channel information acquired by the first received signal processing units 185-1 to 185-4 via the communication control circuit 120, and this channel information Was described as sequentially updating. However, in high-line prospects where channel time fluctuation can be ignored, channel information need not be updated frequently. The first channel information acquisition circuit 131 acquires channel information in advance, for example, before starting service operation, and further stores a transmission weight vector calculated from the value of the channel information (not shown in the figure). However, in this case, the "transmission weight storage circuit" may be implemented and recorded (implemented) and used repeatedly. Also, as an intermediate of these, while the transmission weight vector is basically read out from the first transmission weight storage circuit, the transmission weight vector is updated based on the sequentially acquired channel information, and the updated channel information is updated. It is also possible to have the transmission weight vector updated based on predetermined time intervals.

FIG. 13 is a schematic block diagram showing an example of a configuration of first received signal processing section 185 in base station apparatus 70 according to the related art of the present invention. As shown in FIG. 13, the first received signal processing section 185, antenna element 851-1~851- (N 'and _BS-Ant), a low noise amplifier (LNA) 852-1~852- (N' _{BS- Ant} ), local oscillator 853, mixers 854-1 to 854- (N'BS _-Ant ), filters 855-1 to 855- (N'BS _-Ant ), A / D (analog / digital) conversion Devices 856-1 to 856- (N'BS _-Ant ), an FFT (Fast Fourier Transform) circuit 857-1 to 857- (N'BS _-Ant ), and a first reception weight processing unit 160. And a first received signal processing circuit 158.

The first received signal processing circuits 158-1 to 158-N _SDM (= 4) are connected to the second received signal processing unit 75 shown in FIG. Further, the first received signal processing circuits 158-1 to 158-N _SDM (= 4) and the first received weight processing unit 160 are connected via the second received signal processing unit 75 shown in FIG. The communication control circuit 120 is connected. The first reception weight processing unit 160 includes a first channel information estimation circuit 161 and a first reception weight calculation circuit 162. Similar to the description of the first transmission signal processing unit 181, four first reception signal processing units (185-1 to 185-4) are connected to the base station device 70 in the example of FIG. But give an explanation focusing on one of them.

First, the antenna element 851-1~851- (N 'signals received by the _BS-Ant) is a low noise amplifier 852-1~852- (N' is amplified in _BS-Ant). The amplified signal and the local oscillation signal output from the local oscillator 853 are multiplied by the mixers 854-1 to 854- (N ' _BS -Ant), and the amplified signal is converted from a radio frequency signal to a baseband signal. It is downconverted. Since the downconverted signal includes a signal outside the frequency band to be received, the filters 855-1 to 855- (N'BS _-Ant ) remove out _-of- band components. The signal from which the out-of-band component has been removed is converted to a digital baseband signal by A / D converters 856-1 to 856- (N'BS _-Ant ). For example, in the case of OFDM, digital baseband signals are all input to FFT circuits 857-1 to 857- (N'BS _-Ant ), and predetermined symbol timings determined by a circuit for timing detection whose description is omitted here. The signals on the time axis are converted into signals on the frequency axis (separated into signals of each subcarrier). The signal separated into each subcarrier is input to the first received signal processing circuit 158 and also input to the first channel information estimation circuit 161. Although the circuit for symbol timing detection of OFDM is omitted in FIG. 13, the symbol timing can be grasped by some existing method.

The first channel information estimation circuit 161 is an antenna element of each terminal station apparatus 302 based on a known signal for channel estimation (such as a preamble signal added to the beginning of a radio packet) separated into each subcarrier; Channel information between each antenna element 851 of base station apparatus 70 is estimated for each subcarrier, and the estimation result is output to first reception weight calculation circuit 162. The first reception weight calculation circuit 162 calculates, for each subcarrier, a reception weight vector to be multiplied based on the input channel information. Under the present circumstances, the receiving weight which synthesize | combines the signal received by each antenna element 851-1 to 851- (N'BS _-Ant ) is 1st received signal processing part 185-1-185-N _SDM (= 4) The first reception signal processing units 185-1 to 185-N _SDM are individually calculated.

The first reception signal processing circuit 158 is a signal for each subcarrier (precisely, a signal from a plurality of antenna elements is an element input from the FFT circuits 857-1 to 857- (N ′ _BS -Ant) A reception signal vector) is multiplied by the reception weight (precisely, a reception weight vector having reception weights corresponding to a plurality of antenna elements) input from the first reception weight calculation circuit 162, and the multiplication result Are additively synthesized for each subcarrier. The first reception signal processing circuit 158 outputs a signal obtained by the addition and synthesis to the second reception signal processing unit 75. Here, addition and combining means addition after multiplication of each component of the vector in the vector product for each subcarrier, and the multiplication of the received signal and the reception weight and the entire addition and combination thereof are mathematically vector Corresponds to product processing.

  Note that the reception weight vector multiplied by the first reception signal processing circuit 158 is acquired from the first reception weight calculation circuit 162 provided in the first reception weight processing unit 160 at the time of signal reception processing. The first reception weight processing unit 160 uses the channel information acquired by the first channel information estimation circuit 161, and the first reception weight calculation circuit 162 calculates a reception weight vector. For example, if the terminal station device 302 is transmitting signals to the plurality of antenna elements 851 of the first received signal processing unit 185 in a virtual transmission path corresponding to the first singular value, the terminal station device 302 Is like transmitting toward each first received signal processing unit 185 using one virtual antenna element using the transmission weight for the virtual transmission line corresponding to the first singular value. Channel information on the reception side between the one antenna element and the plurality of antenna elements 851 of the first reception signal processing unit 185, and each component of the reception weight vector for this channel vector is (Weight of maximum ratio combination) or all absolute values may be fixed with respect to the value given by equation (7) (weight of equal gain combination). Alternatively, the channel matrix between the antenna element of the terminal station apparatus 302 and the plurality of antenna elements 851 of the first received signal processing unit 185 of the base station apparatus 70 can be obtained by singular value decomposition One left singular vector may be used as a reception weight vector.

  The first reception weight calculation circuit 162 outputs the reception weight vector calculated in this manner to the first reception signal processing circuit 158. Further, the communication control circuit 120 manages control related to the entire communication, such as management of the transmission source station and overall timing control.

  In the above description, although it is described that the reception weight is sequentially calculated using the channel information acquired in the first channel information estimation circuit 161, if the line-of-sight environment where channel time fluctuation can be ignored is frequent, it is frequently Channel information need not be updated. For example, the first channel information estimation circuit 161 acquires channel information in advance before starting service operation, and stores the reception weight vector calculated from the value of the channel information (not shown in the figure). However, in this case, the “first reception weight storage circuit” may be implemented by a configuration that is mounted and recorded at the subsequent stage of the first reception weight calculation circuit 162), and it may be used repeatedly. In this case, the communication control circuit 120 outputs information indicating the terminal station apparatus or the like of the transmission source to the first reception weight storage circuit that outputs the reception weight. Also, as an intermediate of these, while the reception weight vector is basically read out from the first reception weight storage circuit, the reception weight vector is updated based on the sequentially acquired channel information, and the updated channel information is updated. It is also possible to have a configuration in which the reception weight vector is updated at a predetermined time interval based on that.

  Note that the second reception signal processing unit 75 in FIG. 11 receives the reception signals that are multiplied by the reception weight vector and aggregated into one system from the above-described first reception signal processing units 185-1 to 185-4. However, they are substantially equivalent to the received signal of the 4 × 4 MIMO channel, and it is possible to process the signal sequence spatially multiplexed by the received signal detection process of the prior art. Specifically, 4 × 4 in the case where four sets of signal sequences transmitted on the transmitting side are received by four sets of virtual antennas configured with a plurality of antennas on the receiving side (base station apparatus 70 side) For the MIMO channel of (4), a 4 × 4 channel matrix is acquired for each subcarrier with a known training signal for channel estimation attached to the head of the received signal. The reception weight matrix is calculated based on this channel matrix, and the detection processing of the signal transmitted based on the acquired reception weight matrix is performed. For example, an inverse matrix of ZF (Zero Forcing) type is used, or a reception weight matrix of Maximum Mean Square Error (MMSE) type is used. If there is enough time for signal processing, MLD (Maximum Likelihood Detection) or simplified MLD (QR-MLD) using QR decomposition may be used. Also, in the signal detection processing here, for example, soft decision of the received signal is performed once, deinterleave processing is performed as necessary, and then error correction processing is performed to perform final signal detection. good. The signal detected by this reception signal processing is output to the MAC layer processing circuit 78, is subjected to processing of a predetermined MAC layer, and is output to the network side through the interface circuit 77.

  In addition, the MAC layer processing circuit 78 performs processing related to the MAC layer (for example, conversion of data input to and output from the interface circuit 77 and data to be transmitted and received on a wireless circuit, that is, wireless packet, termination of header information of the MAC layer Etc.). Although the scheduling processing circuit 781 is substantially unnecessary in the case of point-to-point communication, in the case of performing point-to-multipoint communication with a plurality of terminal stations 302, It performs various types of scheduling processing to select the terminal station apparatus 302 that performs communication, and outputs the scheduling result to the communication control circuit 120. The received data processed by the MAC layer processing circuit 78 is output to an external device or network via the interface circuit 77.

  Further, the communication control circuit 120 manages control related to the entire communication, such as management of the terminal station apparatus 302 of the transmission source and overall timing control. Further, information indicating the terminal station apparatus or the like of the transmission source is input from the communication control circuit 120 to the first reception weight processing unit 160 that performs signal processing related to the calculation of the reception weight described above.

As for signal reception, as in the case of transmission, in the wideband system using the OFDM modulation method or SC-FDE method, the multiplication of the above-mentioned reception weight is performed for each subcarrier. That is, the FFT circuits 857-1 to 857- (N'BS _-Ant ) perform FFT on the signals output from the A / D converters 856-1 to 856- (N'BS _-Ant ) to each subcarrier. Signal processing in the first channel information estimation circuit 161 and reception signal processing in the first reception signal processing circuit 158 are performed for each of the separated and separated subcarriers.

The above is the description of the base station device 70 in the related art of the present invention. Here, it is important that the local oscillator 815 in the first transmission signal processing unit 181 is common to the mixers 816-1 to 816-(N ′ _BS -Ant) in each antenna system in the same first transmission signal processing unit 181. On the other hand, the local oscillator 815 is not shared between the first transmission signal processing units 181 which are different. Similarly, the local oscillator 853 in the first received signal processing unit 185 is shared by the mixers 854-1 to 854- (N ' _BS -Ant) in each antenna system in the same first received signal processing unit 185. On the other hand, it is also important that the local oscillator 853 is not shared between the different first received signal processing units 185. As shown in FIG. 10, generally, the first transmission signal processors 181-1 to 181-4 (the first signal processors 304-1 to 304-4 in FIG. 10) are physically separated by several meters. In a high frequency band such as a millimeter wave, it is assumed that the loss is about 10 dB per meter or more when routed through a cable. Since there are a large number of antenna elements connected to the first transmission signal processing unit 181 and the first reception signal processing unit 185, it is necessary to branch and input signals to the mixers 816 and 854 in a plurality of systems, Considering the drop in the level due to this branching, the loss of the cable length of several meters can not be ignored, so it is closed in the individual first transmission signal processing unit 181 and the individual first reception signal processing unit 185 to be local. A configuration in which the oscillators 815 and 853 are shared and not shared between different first transmission signal processing units 181 and first reception signal processing units 185 is effective.

  Here, although each antenna adjusts the phase of transmission / reception signals for directivity control, the same first transmission signal processing units 181-1 to 181-4 (the first signal processing unit in FIG. 10) In 304-1 to 304-4), it is easy to make the phase relationship of the signal inputted from each of the local oscillator 815 or the local oscillator 853 constant at all times, so that the local oscillator 815 or the local oscillator 853 can It is possible to determine what phase relationship should be multiplied by the transmission / reception weight so that the part does not depend. However, when the local oscillator 815 uses a plurality of asynchronous ones in the first transmission signal processing unit 181 (or the local oscillator 853 in the first reception signal processing unit 185), at least the first transmission signal When multiplying the transmission weight in the processing unit 181, it is necessary to adjust in consideration of the complex phase relationship between the plurality of local oscillators 815 (or 853), and if this adjustment is not made, directivity control functions effectively I will not do. Care should be taken in this regard in the design of the device. In the related art of the present invention, the same first transmission signal processing unit 181 shares the local oscillator 815 for the reason described above, and the same first reception signal processing unit 185 shares the local oscillator 853 for the reason described above However, it is not necessary to implement complete signal separation on the transmit side as in multi-user MIMO, as signal separation between the four systems of spatially multiplexed signals can be performed on the receive side.

  Although a plurality of signal sequences can basically be separated by signal processing on the reception side in this way, for example, the phases among the first transmission signal processing units 181-1 to 181-4 by feedback of a channel or the like. If the relationship is known, it is also possible to multiply (ie, transmit precoding) the transmit weight matrix of signal separation beforehand at the transmit side. In this case, the second transmission signal processing unit 71 of the base station device 70 multiplies this transmission weight matrix. The transmission weight matrix is calculated using calibration processing based on uplink channel information on the four signal sequences after multiplication by the reception weight vector acquired by the second reception signal processing unit 75. It does not matter. However, as described above, the terminal station apparatus 302 on the receiving side can acquire the channel matrix by the training signal added to the transmission signal even in the downlink, so if the signal processing on the receiving side is used, the second process is not always necessary. The multiplication of the transmission weight matrix in the transmission signal processing unit 71 is not necessary.

(About the circuit configuration of the terminal station device 60 corresponding to the terminal station device 302 in the related art of the present invention)
FIG. 14 is a schematic block diagram showing an example of a configuration of the terminal station device 60 corresponding to the terminal station device 302 in the related art of the present invention. As shown in FIG. 14, the terminal station device 60 includes a transmitting unit 61, a receiving unit 65, an interface circuit 67, a MAC (Medium Access Control) layer processing circuit 68, and a communication control circuit 121.

  The terminal station device 60 inputs / outputs data to / from an external device or network via the interface circuit 67. The interface circuit 67 detects data to be transferred on the wireless channel among the input data, and outputs the detected data to the MAC layer processing circuit 68. The MAC layer processing circuit 68 performs processing related to the MAC layer in accordance with an instruction of the communication control circuit 121 which performs management control of the entire operation of the terminal station device 60. Here, the processing related to the MAC layer includes conversion of data input / output by the interface circuit 67, data transmitted / received on the wireless circuit, that is, wireless packet, addition of header information of the MAC layer, and the like. In MIMO transmission, since signals are space-multiplexed and transmitted to one terminal station apparatus 60, a plurality of signal sequences are output from the MAC layer processing circuit 68 to the transmission unit 61.

FIG. 15 is a schematic block diagram showing an example of the configuration of the transmission unit 61 in the terminal station device 60 in the related art of the present invention. As illustrated in FIG. 15, the transmission unit 61 includes transmission signal processing circuits 811-1 to 811-N _SDM (N _SDM is an integer of 2 or more), and addition synthesis circuits 812-1 to 812-N _MT-Ant (N _MT-Ant is an integer of 2 or more), IFFT (Inverse Fast Fourier Transform: Inverse Fast Fourier Transform) & GI (Guard Interval: Guard Interval) applying circuit 813-1 to 813-N _MT-Ant , D / A (digital / Analog) converter 814-1 to 814-N _MT-Ant , local oscillator 815, mixers 816-1 to 816-N _MT-Ant , filters 817-1 to 817-N _MT-Ant , high power amplifier (HPA) and _{818-1~818-N MT-Ant,} an antenna element _{819-1~819-N MT-Ant,} a first transmission weight processing unit 140 It is provided. A transmission signal processing circuit _{811-1~811-N SDM,} the first transmission weight processing unit 140, and a communication control circuit 121 shown in FIG. 14.

The first transmission weight processing unit 140 includes a channel information acquisition circuit 141, a channel information storage circuit 142, and a first transmission weight calculation circuit 143. Here, _{N SDM} subscripts of the transmission signal processing circuit _{811-1~811-N SDM} in FIG 15 represents a multiplex number for performing spatial multiplexing simultaneously. In addition, the N _MT-Ant of the suffix of the circuit from the addition synthesis circuit 812-1 to 812-N _MT-Ant to the antenna element 810-1 to 819-N _MT-Ant is the number of antenna elements included in the terminal station apparatus 60. Represents N _{MT -Ant} is, for example, 16.

In the related art of the present invention, since one terminal station device 60 spatially multiplexes and transmits signals to the base station device 70, a plurality of signal sequences are input from the MAC layer processing circuit 68 to the transmitting unit 61 and input The signal sequences of the plurality of systems are input to the transmission signal processing circuits 811-1 to 811-N _SDM . When the transmission signal processing circuit 811-1 to 811-N _SDM receives data (data input # 1 to #N _SDM ) to be transmitted by the wireless channel to the destination base station apparatus 70 from the MAC layer processing circuit 68, Modulates the input data. Here, for example, if the OFDM modulation method is used, modulation processing is performed on the signal of each signal sequence for each subcarrier. Furthermore, the transmission weight is multiplied for each subcarrier by the baseband signal subjected to the modulation processing. The signal multiplied by the transmission weight corresponding to each antenna element 819-1 to 819-N _MT-Ant is subjected to the remaining signal processing as necessary, and each transmission signal processing as sampling data of the transmission signal in the baseband The circuits 811-1 to 811 -N _SDM input to the adding and combining circuits 812-1 to 812 -N _MT -Ant.

The signals input to the adding and combining circuits 812-1 to 812-N _MT-Ant are combined for each subcarrier. The synthesized signal is converted from the signal on the frequency axis to the signal on the time axis by the IFFT & GI application circuits 813-1 to 813-N _MT-Ant , and further insertion of guard intervals or between OFDM symbols (SC-FDE If it is Single-Carrier Frequency Domain Equalization), processing such as waveform shaping between blocks in block transmission is performed, and D / A converter 814-1 is applied to each of antenna elements 819-1 to 819-N _MT-Ant. At 814-N _MT-Ant , digital sampling data is converted to a baseband analog signal. Furthermore, each analog signal is multiplied by the local oscillation signal input from the local oscillator 815 by the mixers 816-1 to 816 -N _MT-Ant , and is upconverted to a radio frequency signal. Here, since the upconverted signal includes the signal in the region outside the band of the channel to be transmitted, the filter 815-1 to 817-N _MT-Ant removes the signal out of the band and should be transmitted. A signal is generated. The generated signal is amplified by the high-power amplifier _{818-1~818-N MT-Ant,} and transmitted from the antenna elements _{819-1~819-N MT-Ant.}

In FIG. 15, after the addition synthesis of the signals of the respective subcarriers is performed by the addition synthesis circuit 812-1 to 812-N _MT-Ant , processes such as IFFT processing, guard interval insertion, and waveform shaping are performed. . However, it is assumed that the transmission signal processing circuits 811-1 to 811-N _SDM perform these processes, and that the addition / synthesis circuits 812-1 to 812-N _MT-Ant synthesize the IFFTed sampling signals on the time axis. The IFFT & GI application circuits 813-1 to 813-N _MT-Ant may be omitted (strictly, they may be included in the transmission signal processing circuits 811-1 to 811-N _SDM ). In this case, the rest of the signal processing necessary after transmission weight multiplying in the transmission signal processing circuit _{811-1~811-N SDM} refers IFFT processing, insertion of the guard interval, the process of waveform shaping or the like.

In addition, the transmission weights to be multiplied by the transmission signal processing circuits 811-1 to 811-N _SDM are acquired from the first transmission weight calculation circuit 143 provided in the first transmission weight processing unit 140 at the time of signal transmission processing. Be done. In the first transmission weight processing unit 140, the channel information acquisition circuit 141 separately acquires channel information acquired by the reception unit 65 via the communication control circuit 121, and while sequentially updating this, the channel information storage It is stored in the circuit 142. At the time of signal transmission, the first transmission weight calculation circuit 143 reads channel information corresponding to the destination station from the channel information storage circuit 142 in accordance with an instruction from the communication control circuit 121, and calculates transmission weight based on the read channel information. Do. The first transmission weight calculation circuit 143 outputs the calculated transmission weight to the transmission signal processing circuits 811-1 to 811-N _SDM . Note that, in normal communication, since the other party with which the terminal station apparatus communicates is limited to a specific base station apparatus, in the above description, management regarding the terminal station apparatus to be the destination is explicitly shown. Naturally, it is also possible to perform the processing as being one.

  The feature of the related art of the present invention is that the first singular value is calculated between the terminal station apparatus 60 and the first transmission signal processing units 181-1 to 181-4 of the base station apparatus 70 in the calculation of the transmission weight. Using a virtual transmission path corresponding to There are several variations in the channel estimation method and transmission / reception weight calculation method in the case of utilizing the virtual transmission path corresponding to the first singular value, and the method for efficiently acquiring this will be described in detail later. Do. For example, the first right singularity when singular value decomposition is performed on each channel matrix in the uplink from the terminal station device 60 to the first transmission signal processing units 181-1 to 181-4 of the base station device 70. A vector may be used as a transmission weight vector. In this case, the first transmission weight calculation circuit 143 has a function of calculating the first right singular vector.

  Alternatively, when the base station apparatus 70 multiplies the plurality of antenna elements of each of the first transmission signal processing units 181-1 to 181-4 by a predetermined transmission weight vector for signal transmission, in fact, Equivalently to one in which each of the first transmission signal processing units 181-1 to 181-4 transmits from one virtual antenna element in spite of being transmitted from a plurality of transmission antennas It is. Therefore, the vector of channel information between this one virtual antenna element and each receiving antenna of the terminal station apparatus 60 is acquired, and the uplink processing is performed by the implicit feedback method of performing calibration processing on this channel vector. It is also possible to obtain channel information of The first transmission weight calculation circuit 143 calculates a vector obtained by taking the complex conjugate of the channel vector as shown in equation (7) based on the uplink channel vector thus obtained, or each component of the vector. Any of vectors in which the absolute values of all are made constant may be used as the transmission weight vector.

  As an alternative to this, the first transmission weight calculation circuit 143 is provided between the terminal station apparatus 60 and one antenna element in the first transmission signal processing units 181-1 to 181-4 of the base station apparatus 70. The channel vector of the channel information on the receiving side is obtained by using and either the vector obtained by taking the complex conjugate of this channel vector as shown in equation (7) or the vector in which all absolute values of each component of the vector are made constant. It may be used as a transmission weight vector. Further, the communication control circuit 121 manages control related to the entire communication such as the entire timing control.

FIG. 16 is a schematic block diagram showing an example of the configuration of the receiving unit 65 in the terminal station device 60 in the related art of the present invention. As shown in FIG. 16, the receiving unit 65 includes antenna elements 851-1 to 851-N _MT-Ant , low noise amplifiers (LNA) 852-1 to 852-N _MT-Ant , a local oscillator 853 and a mixer 854. -1 to 854-N _MT-Ant , filter 855-1 to 855-N _MT-Ant , A / D (analog / digital) converters 856-1 to 856-N _MT-Ant , FFT (Fast Fourier) Transform (Fast Fourier Transform) circuits 857-1 to 857-N _MT-Ant , received signal processing circuits 145-1 to 145-N _SDM, and a first reception weight processing unit 144. The reception signal processing circuits 145-1 to 145-N _SDM and the first reception weight processing unit 144 are connected to the communication control circuit 121 shown in FIG. The first reception weight processing unit 144 includes a first channel information estimation circuit 146 and a first reception weight calculation circuit 147.

Signals received by antenna elements _{851-1~851-N MT-Ant} is amplified by the low noise amplifier _{852-1~852-N MT-Ant.} The amplified signal and the local oscillation signal output from local oscillator 853 are multiplied by mixers 854-1 to 854-N _MT-Ant , and the amplified signal is downconverted from the radio frequency signal to the baseband signal. Ru. Since the downconverted signal includes a signal outside the frequency band to be received, the filters 855-1 to 855-N _MT-Ant remove out _- of-band components. The signal from which the out-of-band component has been removed is converted into a digital baseband signal by A / D converters 856-1 to 856-N _MT-Ant . For example, in the case of using OFDM, digital baseband signals are input to FFT circuits 857-1 to 857-N _MT-Ant , and time is determined at a predetermined symbol timing determined by a circuit for timing detection which is not described here. The on-axis signal is converted into a signal on the frequency axis (separated to the signal of each subcarrier). The signals separated into the respective subcarriers are input to the reception signal processing circuits 145-1 to 145 -N _SDM and also to the first channel information estimation circuit 146.

The first channel information estimation circuit 146 performs a first transmission of the base station apparatus 70 based on a known signal for channel estimation (such as a preamble signal added to the beginning of a radio packet) separated into each subcarrier. Channel information between a virtual antenna element formed by each transmission weight vector of the signal processing units 181-1 to 181-4 and each antenna element 851-1 to 851-N _MT-Ant of the terminal station device 60 A channel vector is estimated for each subcarrier, and the estimation result is output to the first reception weight calculation circuit 147. The first reception weight calculation circuit 147 calculates the reception weight for each subcarrier based on the input channel information. For this reception weight, for example, as described above, a ZF type pseudo inverse matrix is used, or an MMSE type reception weight matrix is used. At this time, the reception weight vector for combining the signals received by each of the antenna elements 851-1 to 851-N _MT-Ant differs for each signal sequence, and the above-mentioned ZF pseudo inverse matrix or MMSE type reception It corresponds to a row vector such as a weight matrix and is respectively input to the received signal processing circuits 145-1 to 145-N _SDM corresponding to the signal sequence to be extracted.

Reception signal processing circuits 145-1 to 145 -N _SDM is supplied from first reception weight calculation circuit 147 to the signal for each subcarrier input from FFT circuits 857-1 to 857 -N _MT-Ant . The reception weight is multiplied, and the multiplication result is added and synthesized for each subcarrier. The received signal processing circuits 145-1 to 145-N _SDM perform demodulation processing on each of the signals obtained by the addition and synthesis, and output the reproduced data to the MAC layer processing circuit 68.

Here, in the reception signal processing circuits 145-1 to 145-N _SDM , signal processing of different signal sequences is performed. Further, MLD, a simplified MLD using QR decomposition, or the like may be used as received signal processing across a plurality of received signal processing circuits 145-1 to 145-N _SDM . In addition, the MAC layer processing circuit 68 performs processing related to the MAC layer (for example, conversion of data input to or output from the interface circuit 67 and data to be transmitted / received on a wireless circuit, that is, wireless packet, Etc.). The received data processed by the MAC layer processing circuit 68 is output to an external device or network via the interface circuit 67. Further, the communication control circuit 121 manages control related to the entire communication such as the entire timing control.

  Here, as in the case of the transmitting side, the terminal station apparatus 60 at the time of reception can also perform signal processing in which a virtual transmission path corresponding to the first singular value is consciously used. An example of another structure of the receiving part 65 in the terminal | end station apparatus 60 in related technology of this invention is shown in FIG.

In FIG. 17, reference numeral 154 is a first reception weight processing unit, reference numeral 155 is a first reception signal processing circuit, reference numeral 156 is a first channel information estimation circuit, reference numeral 157 is a first reception weight calculation circuit, and reference numeral 159 Denotes a second reception signal processing circuit, and the other is the same as FIG. In the above description, although it has been described that the first reception weight calculation circuit 157 calculates the reception weight for direct signal separation of the signal sequence of the N _SDM system, it is temporarily assumed that it corresponds to the first singular value. While performing signal separation in the transmission path, it is also possible to remove residual interference between signal sequences that still remain in two steps.

  In this case, the first reception weight calculation circuit 157 is, for example, directed from each antenna element of the first transmission signal processing units 181-1 to 181-4 of the base station apparatus 70 to each antenna element of the terminal station apparatus 60. When channel information can be acquired, a first left singular vector at the time of singular value decomposition is calculated as a reception weight vector for a channel matrix having this channel information as a component. Alternatively, in the case where signal transmission is performed using one virtual antenna element formed by multiplying the transmission weight vectors by the first transmission signal processing units 181-1 to 181-4, A channel vector between the corresponding virtual antenna element and each antenna element of the terminal station device 60 may be determined, and each component of the reception weight vector may be determined by equation (7) based on this vector (maximum ratio combining) Of all the absolute values with respect to the value given by equation (7) or (7) may be made constant (weight of equal gain combination).

Then, the first reception weight calculation circuit 157 outputs the reception weight vector thus obtained to each of the first reception signal processing circuits 155-1 to 155-N _SDM . However, since signal processing for separating residual interference is performed in the second received signal processing circuit 159 at this later stage, it is not necessary to frequently update the reception weight vector in real time, for example, a line of sight of about 100 ms period It is also possible to reuse the common receive weight vector in the time domain where it is expected that the wave channel information will not fluctuate rapidly.

The first channel information estimation circuit 156 and the first reception weight calculation circuit 157 do not update the reception weight sequentially from such a viewpoint, for example, the first channel information estimation circuit 156 The channel estimation accuracy is improved by averaging, and the first reception weight calculation circuit 157 calculates the first reception weight vector at a predetermined cycle based on the averaged channel information, and the first reception weight vector is calculated. It is also possible to input to the received signal processing circuits 155-1 to 155-N _SDM . In this case, the channel information may be regarded as relative channel information (or each channel information divided by the channel information of the reference antenna) based on the complex phase of the reference antenna (for example, the first antenna) in averaging. It is preferable to utilize

The first received signal processing circuits 155-1 to 155 -N _SDM output signals from the virtual transmission line corresponding to these first singular values to the second received signal processing circuit 159. The division of functions between the first received signal processing circuits 155-1 to 155-N _SDM and the second received signal processing circuit 159 is performed by the first received signal processing unit 185 of the base station apparatus 70 shown in FIG. Similar to the relationship with the second received signal processing unit 75. That is, a signal obtained by reducing the signal of a huge reception signal corresponding to the number NMT _-Ant of antenna elements into the number N _SDM of signal sequences spatially multiplexed by the first reception signal processing circuits 155-1 to 155-N _SDM To the second received signal processing circuit 159, and the second received signal processing circuit 159 performs general MIMO signal processing in a space whose dimension is reduced.

Specifically, the second received signal processing circuit 159 refers to a known training signal added at the beginning of the received signal, and acquires a channel matrix of N _SDM × N _SDM for the signal sequence of the N _SDM system. And perform reception signal detection processing based on the channel matrix. As described above, the second reception signal processing circuit 159 multiplies an inverse matrix of ZF type or a linear reception weight matrix of MMSE type, or non-linear such as MLD or simple MLD (QR-MLD etc.) Signal processing can also be performed. The second reception signal processing circuit 159 performs demodulation processing on the signal of the N _SDM system thus signal-separated, and outputs the reproduced data to the MAC layer processing circuit 68. This is equivalent to the signal processing of the second received signal processing unit 75 of the base station apparatus.

FIG. 18 shows an example of the device configuration in the second received signal processing unit 75 of the base station device 70 or the second received signal processing circuit 159 of the terminal station device 60 (basically, the processing is performed by the base station device and the terminal station device (Common). The basic operation of the second received signal processing circuit 190 is as described above, N _SDM signal sequence N _SDM sequence as a received signal of the virtual transmission path corresponding to the first singular value of the second reception is input to the signal processing circuit 190 (corresponding to the second received signal processing circuit 159 in FIG. 17), with reference to the known training signal channel matrix acquiring circuit 191 is applied to the head of the received signal, N _SDM system Obtain a channel matrix of N _SDM × N _SDM for a signal sequence of Reception weight matrix calculation circuit 192 calculates a reception weight matrix as a ZF inverse matrix or an MMSE linear reception weight matrix based on the channel matrix, and outputs this to reception weight matrix multiplication circuit 193. The reception weight matrix multiplication circuit 193 multiplies subsequent data by the reception weight matrix to suppress an interference signal which is a crosstalk component between different virtual transmission paths. The signal detection circuit 194 performs signal detection on each signal whose SINR characteristic has been enhanced. Signal detection here is intended for general demodulation processing. For example, the signal detection circuit 194 performs soft decision on the received signal, performs error correction after deinterleaving, and performs final signal detection. Data expanded and parallel-transmitted into a plurality of signal sequences are converted into one-sequence data by parallel / serial conversion, and these are output to the MAC layer processing circuit. Although an example of linear signal processing is shown here as a typical example, the signal detection circuit 194 can also perform non-linear signal processing such as MLD to QR-MLD.

Note that the second transmission signal processing circuit 148 may be provided also in the terminal station device 60 so that the second transmission signal processing unit 71 is provided in the base station device 70 shown in FIG. FIG. 19 is a diagram showing a different configuration example of the transmission unit 61 of the terminal station device 60 in the related art of the present invention. The transmission unit 61 further includes a second transmission signal processing circuit 148, and includes first transmission signal processing circuits 821-1 to 821-N _SDM instead of the transmission signal processing circuits 811-1 to 811-N _SDM , Furthermore, instead of the first transmission weight calculation circuit 143, a transmission weight calculation circuit 149 is provided. In this case, the second transmission signal processing circuit 148 has the function of the second transmission signal processing unit 71 shown in FIG. Specifically, the second transmission signal processing circuit 148 generates a radio packet to be transmitted by a radio channel and performs a modulation process, and a signal between virtual transmission paths corresponding to each first singular value. The transmission weight matrix for compensating for the leak of the data is acquired from the transmission weight calculation circuit 149, and the transmission signal vector of the N _SDM system is multiplied by the transmission weight matrix (transmission precoding), and N obtained by the processing The transmission signal of the _SDM system is output to the first transmission signal processing circuit 821.

The first transmission signal processing circuits 821-1 to 821-N _SDM are virtual transmission paths corresponding to the first singular value for each of the transmission signals of the N _SDM system input from the second transmission signal processing circuit 148. Multiply the transmit weights to form. Here, as a function of the transmission weight calculation circuit 149, the first transmission signal processing circuits 821-1 to 821-N _SDM calculate transmission weights for forming a virtual transmission line corresponding to the first singular value. And a function for calculating a transmission weight matrix for compensating for signal leakage between virtual transmission paths corresponding to the respective first singular values. The transmission weight matrix in this case is obtained based on channel information acquired by, for example, a method using implicit feedback with calibration processing or a method using direct explicit feedback.

  The feature of the related art of the present invention relates to a virtual transmission path corresponding to the first singular value between the first transmission signal processing units 181-1 to 181-4 of the base station apparatus 70 and the terminal station apparatus 60. It is to use. Therefore, with respect to each channel matrix from terminal station apparatus 60 toward first transmission signal processing units 181-1 to 181-4 of base station apparatus 70, the transmission weights are set to the first right singular vector when singular value decomposition is performed. By using a vector, the first transmission weight calculation circuit 143 has a function of calculating the first right singular vector. As an approximate solution of this first right singular vector, although it will be described in detail later, between the one of the first transmission signal processing units 181-1 to 181-4 of the base station apparatus 70 and one antenna element. A channel vector may be determined, and either a vector obtained by taking a complex conjugate of this channel vector or a vector in which all absolute values of the components of the vector are fixed may be used as the transmission weight vector. Essentially, the antenna element groups of the first transmission signal processing units 181-1 to 181-4 of the base station device 70 form a virtual directional antenna as a whole, but as an alternative, for example, this method It is equivalent to considering the case where it represents with one antenna which exists near the center physically among antenna element groups as an approximate solution. In this case, although the weight of the approximate solution is different from the weight of the exact solution, the gain obtained as a result of evaluation by simulation does not necessarily have an extremely large deterioration as described later.

The above is the description of the configurations of the terminal station device 60, the transmitting unit 61, and the receiving unit 65 in the related art of the present invention. The important point here is that the local oscillator 815 in the transmitter 61 is shared by the mixers 816-1 to 816 -N _MT-Ant in each antenna system of the transmitter 61, and the local oscillator 853 in the receiver 65 is a receiver The mixers 854-1 to 854-N _MT-Ant in each of the 65 antenna systems are common points. In directivity control, the phases of transmission and reception signals are adjusted for each antenna element, but by making the phase relationship of the signals input from each local oscillator 815 or local oscillator 853 always be constant, It is possible to determine whether the transmission / reception weights should be multiplied with the same phase relationship. On the other hand, when the local oscillator 815 or the local oscillator 853 uses a plurality of asynchronous ones in the transmission unit 61 or in the reception unit 65, directivity control in which at least the transmission weight is multiplied in the transmission unit 61 functions effectively. It disappears. Care should be taken in this regard in the design of the device. It is also possible to share the local oscillator 815 and the local oscillator 853.

(About extension to Point-to-Multipoint)
In the above description, since the explanation has been made centering on the point-to-point type wireless entrance circuit, if the arrangement of the first signal processing unit 304 is operated in an optimized state by some method, the first signal is processed. Spatial multiplexing transmission as many as the number of processing units 304 is possible. The optimization method for this purpose may be antenna arrangement method calculated based on channel orthogonalization conditions, and while setting it at several places at the time of antenna installation, searches the arrangement where virtual transmission paths are almost orthogonal May correspond. However, when one base station apparatus 70 and a plurality of terminal station apparatuses 60 simultaneously perform point-to-multipoint communication, an ideal antenna arrangement on the base station apparatus 70 side is common to all the terminal station apparatuses. Configuration is difficult, so a redundant number of first signal processing units 304 are installed, and the configuration is such that communication is performed by selecting a different combination of first signal processing units 304 for each terminal station apparatus 60 to communicate with. It does not matter. In this case, since the communication control circuit determines the optimum combination of the first signal processing units 304, the communication control circuit combines the optimum first signal processing units 304 for each terminal station apparatus 60. It is necessary to have functions such as a database for information.

For example, in the technique described in reference 1, a plurality of sub-arrayed first signal processing units 304 are disposed above the wall of a building, and the terminal station devices located below are irradiated from above in a line-of-sight environment Is explained. By configuring the base station apparatus side with the first signal processing unit 304 formed into a plurality of subarrays in this way, it is possible to expand the antenna aperture length of the entire subarray to realize stable MIMO transmission. It becomes effective. However, securing the antenna aperture length on the terminal station device side as used in the evaluation in this reference 1 takes into consideration the shape of the current smartphone, etc., and in the direction in which the direct wave arrives from the base station device side The screen is set large, and it is unrealistic to secure such evaluation conditions. Therefore, in an access-based radio communication system that performs MIMO transmission in a communication environment in which a line of sight wave is dominant as shown in Reference 1, the antenna aperture length on the base station apparatus side as in the background art and related art of the present invention A technique for further increasing the transmission capacity by similarly securing the antenna aperture length in the direction in which the direct wave arrives from the base station side stably on the terminal side as well. Is required.
[Reference 1] Atsushi Ota, Takuto Arai, Hirofumi Shirato, Kazuki Maruta, Akihiko Iwakuni, Masataka Iizuka, "Line-of-sight Environment Millimeter-wave Space Multiplexing Transmission Technology Using Parallel Transmission of the First Eigenmode-System Proposal And basic characteristic evaluation results ~ ", Technical Report of IEICE, Radio Communication System (RCS), Vol. 115, no. 181, August 10, 2015, p. 73-p. 78

(About the processing flow of signal processing in the related art of the present invention)
The processing flow of signal processing in the related art of the present invention will be described below. Although the signal processing flow of the base station apparatus and the terminal station apparatus is basically the same, the names and code numbers of circuits to be referred to are different, so here, the signal processing flow regarding the base station apparatus will be described as an example. In addition, as described above, the signal processing in the second transmission signal processing unit 71 (corresponding to the second transmission signal processing circuit 148 in FIG. 19 having an explicit description in the terminal station apparatus) is a transmission weight matrix. It is also possible not to apply the multiplication (transmission precoding) of H. In this case, the part regarding the signal processing is omissible.

  FIG. 20 is a flowchart showing signal processing at the time of signal transmission in the related art of the present invention. When transmission processing is started, the communication control circuit 120 instructs the first signal processing unit 304 and the second signal processing unit 305 to read out the first transmission weight vector and the second transmission weight matrix. (Step S2601, step S2602).

  The reading of the transmission weight vector and the transmission weight matrix here is, for example, in the case of the point-to-multipoint type communication and in the case of the base station apparatus 70, the terminal station apparatus 60 which is the communication counterpart station differs every time communication. Therefore, every time transmission is performed, read processing is performed. On the other hand, in the case of fixed point-to-point type communication, or when the communication partner station is always fixed to the base station device 70 like the terminal station device 60, the process is omitted even if it is not read every time. Is also possible. However, when the time variation of the channel can not be ignored and the transmission weight is changed each time, it may be read out each time transmission, even if the communication partner is fixed. Alternatively, the transmission weights updated in a predetermined cycle may be read. In addition, when the matrix multiplication in the second transmission weight multiplying circuit in the second signal processing unit 305 is omitted as described above, the reading of the transmission weight matrix in the second signal processing unit 305 becomes unnecessary. .

The second signal processing unit 305 generates a transmission signal for N _SDM systems for spatial multiplexing (step S2603), and multiplies the transmission signal by the second transmission weight matrix (step S2604). The transmission data of the N _SDM system after multiplication is transferred to the corresponding first signal processing unit 304 (step S2605). The second signal processing unit 305 determines whether transmission of transmission data is completed (step S2606). If the transmission of transmission data is not completed (step S2606: NO), the second signal processing unit 305 returns the process to step S2603. If the transmission of transmission data has been completed (step S2606: YES), the second signal processing unit 305 ends the signal processing flow at the time of signal transmission.

On the other hand, the first signal processing unit 304 multiplies the transmission signal (one-dimensional signal) by the transmission weight vector using the transmission weight vector corresponding to itself, which has been read in advance (step S2607), and transmits the transmission antenna A transmit signal vector of several N _Ant dimensions is converted, and transmit signal processing is performed for each antenna system (step S2608).

  For example, when assuming the OFDM modulation scheme, transmission signal generation is performed for each subcarrier and for each OFDM symbol, and multiplication of a transmission weight matrix, multiplication of a transmission weight vector, etc. are all performed separately for each subcarrier. To be done. As transmission signal processing here, IFFT processing is performed on the transmission signal for each subcarrier on the frequency axis, guard intervals are added, waveform shaping between symbols is added as necessary, and sampling on this time axis is performed. Data is D / A converted to generate an analog baseband signal, which is up converted by a mixer, then out-of-band components are removed by a filter, and the signal amplified by a high power amplifier is transmitted from an antenna Is done.

  The above is an example in the case of using the OFDM modulation scheme, but the same is true for other schemes such as SC-FDE, and various conventional communication schemes can basically be applied. Further, the signal processing on the frequency axis is not necessarily required. As described later, in the case where the multiplication of the transmission weight vector is performed on the time axis, sampling using a single transmission weight vector (and matrix) is performed. The transmission weight vector (and matrix) may be multiplied for each data. Further, processing such as error correction coding and interleaving is included in the generation processing of the transmission signal, and is omitted in the description here.

  Next, FIG. 21 is a flowchart showing a first example of signal processing flow at the time of signal reception in the related art of the present invention. When the signal is received, the communication control circuit 120 instructs the plurality of first signal processing units 304 to read out the respective first reception weight vectors (step S2701).

  As in the case of the transmitting side, reading of the receiving weight vector here is, for example, point-to-multipoint communication and in the case of the base station apparatus 70, each time the terminal station apparatus 60 which is the communication counterpart station performs communication. Because it is different, each time transmission is performed, read processing is performed. On the other hand, in the case of fixed point-to-point type communication, or when the communication partner station is always fixed to the base station device 70 like the terminal station device 60, the process is omitted even if it is not read every time It is also possible. However, when the time variation of the channel can not be ignored and the reception weight is changed each time, it may be configured to read out each time transmission, even if the communication partner is fixed. Alternatively, the reception weight updated at a predetermined cycle may be read out.

  Thereafter, when an actual signal is received, the first signal processing unit 304 performs signal reception processing for each antenna system (step S2702). The signal reception processing here is, for example, amplification of a received signal by a low noise amplifier, down conversion processing by a mixer, removal of out-of-band frequency components by a filter, and digital baseband by an A / D converter. Convert to signal sample values. In these received signal processing, for example, in the case of the OFDM modulation method, the signal is cut out for each OFDM symbol, the guard interval is removed, and the signal is converted to a signal on the frequency axis for each subcarrier component by FFT.

  The first signal processing unit 304 multiplies the reception signal vector having the signal of each antenna element as the vector component by the reception weight vector with respect to the signal subjected to the above reception signal processing (step S2703). The result is transferred to the second signal processing unit 305 (step S2704). The first signal processing unit 304 determines whether reception of reception data is completed (step S2705). Here, if the reception data continues further (step S2705: YES), the process returns to the reception signal processing shown in step S2702 to continue the processing, and when the reception data is finished (step S2705: NO) The processing of the signal processing unit 304 of 1 ends.

On the other hand, the second signal processing unit 305 determines whether the signal transferred from the first signal processing unit 304 is, for example, a training signal for channel estimation attached to the beginning of the wireless packet (step S2706). If it is a training signal (step S2706: YES), channel estimation is performed (step S2707), and a second reception weight matrix is generated based on the obtained channel matrix (step S2708). If the signal to be transferred is a data portion that is not a training signal (step S2706: NO), the second signal processing unit 305 generates the second reception weight matrix for the spatially multiplexed number of N _SDM dimensional reception signal vectors. After multiplication (step S2709), signal detection processing is performed after signal separation (step S2710). The signal detection process here means, for example, a process of estimating a transmission signal through soft decision processing, deinterleaving processing, error correction processing and the like on the transmission signal. The signal obtained by the signal detection process of the physical layer is output to the MAC layer processing circuit.

  In addition to the OFDM modulation method, general conventional techniques such as the SC-FDE method can be similarly applied to received signal processing. Furthermore, although the description has been made as signal processing for each subcarrier, it is not necessary to be signal processing on the frequency axis, and multiplication of the reception weight vector and the reception weight matrix is performed on the time axis as described later. In such a case, the reception weight vector and the reception weight matrix may be multiplied for each sampling data using a single reception weight vector and a reception weight matrix. For MIMO signal processing equivalent to, for example, step S2709 of multiplying the second reception weight matrix (and step S2710 of performing signal detection processing after signal separation), the second reception weight matrix is necessarily multiplied as linear signal processing. It is not necessary to do, and it is also possible to apply general MIMO signal detection processing such as QR-MLD or MLD.

  In the above description, it is assumed that the local oscillator 853 used in the first signal processing unit 304 is asynchronous for each first signal processing unit 304 as in the base station apparatus 70, and the second reception weight matrix is a signal. In the case of the terminal station apparatus 60, for example, since the local oscillator 853 used for upconversion processing and / or downconversion processing of all antenna elements is shared, in the case of the terminal station apparatus 60, reception is not always necessary. The second reception weight matrix does not change every time. As described above, when the local oscillator 853 is generally shared and channel fluctuation can be ignored, it is also possible to use the second reception weight matrix acquired in the past.

FIG. 22 is a flowchart showing an outline of a second example of signal processing flow at the time of signal reception in the related art of the present invention. Steps S2801 to S2805 illustrated in FIG. 22 are the same as steps S2701 to S2705 illustrated in FIG. The difference from FIG. 21 is that in the signal processing of the second signal processing unit 305, the second signal processing unit 305 generates the second reception weight matrix from the communication control circuit 120 when signal reception processing is started. Receiving the read instruction, the second reception weight matrix is read (step S2806). After that, when the reception signal is transferred from the first signal processing unit 304, the second signal processing unit 305 multiplies the second reception weight matrix by the space division multiplexing reception signal vector of N _SDM dimensions. (Step S2807) After that, signal detection processing is performed (step S2808). The other signal processing is the same as in FIG.

  As described above, the wireless communication system 50 according to the related art of the present invention includes the base station device 70 (first wireless station device) and the terminal station device 60 (second wireless station device). The base station device 70 includes a plurality of first transmission signal processing units 181, a plurality of first reception signal processing units 185, a second transmission signal processing unit 71, and a second reception signal processing unit 75. Have. The plurality of first transmission signal processors 181 includes a plurality of antenna elements 819. The plurality of first reception signal processors 185 include a plurality of antenna elements 851. The second transmission signal processing unit 71 performs signal processing of wireless communication associated with the plurality of first transmission signal processing units 181. The second received signal processing unit 75 performs signal processing of wireless communication associated with the plurality of first received signal processing units 185. The terminal station device 60 includes a plurality of antenna elements 819, a plurality of antenna elements 851, a transmission unit 61, and a reception unit 65. The transmission unit 61 performs wireless communication with the plurality of first reception signal processing units 185 via the plurality of antenna elements 819. The transmitter 61 wirelessly transmits the plurality of first received signal processors 185 and the second received signal processor 75 associated with the first received signal processor 185 via the plurality of antenna elements 819. Communication may be performed. The receiving unit 65 performs wireless communication with the plurality of first transmission signal processing units 181 via the plurality of antenna elements 851. The receiving unit 65 wirelessly transmits the plurality of first transmission signal processing units 181 via the plurality of antenna elements 851 and the second transmission signal processing unit 71 associated with the first transmission signal processing unit 181. Communication may be performed. The first transmission signal processing unit 181 and the first reception signal processing unit 185 transmit weight vectors and reception weights for the MIMO channel matrix used for wireless communication between the first antenna element group and the second antenna element group. At least one of the vectors is at least one of a first right singular vector and a first left singular vector corresponding to a first singular value of the MIMO channel matrix, or an approximate solution of the first right singular vector and an approximate solution of the first left singular vector Calculated based on at least one of The plurality of first transmission signal processing units 181 and the first reception signal processing unit 185 correspond to the first transmission signal processing unit 181 or the first reception signal processing unit 185 of the transmission weight vector and the reception weight vector. At least one of them is used to transmit one or more independent signal sequences.

  Thus, the base station apparatus 70, the terminal station apparatus 60, the wireless communication system 50, and the wireless communication method according to the related art of the present invention can increase transmission capacity by MIMO in an environment where a line-of-sight environment is dominant. For example, the base station device 70, the terminal station device 60, the wireless communication system 50, and the wireless communication method use the high-order spatial multiplexing and the high frequency band while the line-of-sight environment is dominant in the future wireless communication system in the mobile network. Thus, it is possible to realize a large capacity.

  A base station apparatus 70 as a base station apparatus 303 according to a related art of the present invention includes a first signal processing unit 304 in which antenna elements are bundled in a narrow area, and a second signal processing unit 305 that aggregates them. The first signal processing unit 304 performs closed beamforming in each signal processing unit and does not perform beamforming across different first signal processing units 304. The individual first signal processing unit 304 generates transmission / reception weights for the “virtual transmission line corresponding to the first singular value” that makes full use of the “line of sight wave”, and performs a plurality of first signal processing Spatial multiplexing transmission is performed using the individual transmission and reception weights in the unit 304.

  Here, in the above description, it has been described that the perspective environment is the dominant environment as a typical related technology, but even if it is not a perfect perspective environment, for example, a very strong reflected wave comes from a specific direction. In the case where a diffracted wave that is comparable to the line-of-sight wave arrives, a virtual transmission path corresponding to the first singular value is formed in the incoming direction. In this sense, the virtual transmission line corresponding to the first singular value is not necessarily a transmission line configured by a line-of-sight wave, and multiple systems of the virtual transmission line corresponding to the first singular value are actively used. Because it is to spatially multiplex transmission, it is applicable even in an out-of-sight environment. The circuit configuration and the processing flow in that case can be applied as they are without changing the above description at all.

(Antenna placement conditions for orthogonalization of line-of-sight MIMO transmission)
Here, the conditions for the plurality of virtual transmission paths to be substantially orthogonal are organized. In FIG. 10, since one directional beam is effectively formed for every 25 antenna elements, this approximately uses one antenna (for example, a parabolic antenna) having a very high directional gain. It corresponds to what you do. FIG. 23 is a diagram showing a case where the base station apparatus is provided with four parabolic antennas and the terminal station apparatus is provided with 16 linear array antenna elements. In FIG. 23, reference numeral 306 denotes a base station apparatus, reference numeral 302 denotes a terminal station apparatus, and reference numerals 307-1 to 307-4 denote parabola antennas. The terminal station device 302 corresponds to the terminal station device 60. The base station device 306 corresponds to the base station device 70. Basically, transmission equivalent to the parabola antennas 307-1 to 307-4 shown in FIG. 23 is realized by grouping a large number of antenna elements of the base station apparatus 70.

  Here, the conditions in which the four singular values of the MIMO channel in FIG. 23 in which the line-of-sight wave is dominant become substantially equally large values are arranged as in the case described above. For example, although the conditions under which MIMO transmission in a line-of-sight environment is established are defined in the patent document (Japanese Patent No. 5488894), the basic idea of these conventional techniques is the antenna provided in the base station apparatus and the terminal station apparatus. The distance between the elements is increased as much as possible, and as a result, the distance between each transmitting antenna and the receiving antenna is dispersed, and the difference in the distance becomes a pseudo random relationship (or predetermined relationship). It tries to adjust in the same way.

  On the other hand, for example, in the phased array antenna technology, if the distance between the antenna elements of a linear linear array is d, the value of d is set small, as seen from an antenna at a distance in the direction in which the directivity should be directed. Radio waves arriving at (or sent out) antenna elements of individual linear arrays can be approximated as plane waves, and if the direction of incoming waves is represented by angle θ, the path difference for each antenna element is high at d · sin θ It can be approximated to the accuracy. However, in order to set the distance between the antenna elements as wide as possible according to the basic idea of the above-mentioned prior art, such plane wave approximation can not be performed, and the approximation needs to be performed under different conditions. The As a result, the accuracy of the prior art approximation is reduced. In fact, when performing MIMO communication in a line-of-sight environment, both transmitting and receiving stations assumed large parabolic antennas. Usually, since the size of the parabolic antenna is much larger than the wavelength, it is not possible to approximate the plane wave with the accuracy with which the above-mentioned path length difference can be ignored with respect to the wavelength.

However, while the effective aperture length of the antenna on the base station apparatus 70 side is extended, the distance between the antenna elements on the terminal station apparatus 60 side is about several wavelengths (the distance between the base station apparatus 70 and the terminal station apparatus 60). For example, if it is set to the order of 3 wavelengths or less, the path difference for each antenna element on the terminal station apparatus 302 side from the parabola antenna on the base station apparatus 306 side in FIG. It becomes possible to approximate. Therefore, as shown in FIG. 24, a terminal station corresponding to the base station apparatus antenna #j (310-j) (1 ≦ j M M) of the base station apparatus 70 corresponding to the base station apparatus 306 and the terminal station apparatus 302 Assuming that the distance between the terminal station apparatus antenna # 1 (320-1) of the apparatus 60 is L _j and the angle difference between the terminal station apparatus antenna # 1 (320-1) and the front direction is θ _j , Between the channel matrix (base station apparatus antenna #j of the base station apparatus 70 to the terminal station apparatus antenna #i (1.ltoreq.i.ltoreq.N _{MT -Ant} ) antenna of the terminal station apparatus 60 using the spacing d of the terminal station apparatus antenna When channel information is represented by h _ij ), it can be approximately represented by the following equation (15). In Equation (15), N _{MT -Ant} is denoted as N in order to avoid complication. Further, although the number of parabolic antennas 307-1 to 307-4 included in the base station apparatus 306 is four in FIG. 23, the number of antenna elements included in the base station apparatus 306 is represented as M in equation (15).

Although the channel matrix H is expressed in the form of a product of matrices in equation (15), the (j, j) component of the matrix of the second item is the jth antenna of the base station apparatus 70 and the first antenna of the terminal station apparatus 60 And channel information between The difference information of each component of the N _{MT -Ant} antennas of the terminal station device 60 corresponds to the column vector of the j-th column of the matrix of the first item. Since the (j, j) component of the second item is a common term applied to all components of the column vector, if the column vectors of the first item are orthogonal, each singular value is stably large and Become. The condition that the i-th column vector of the first term and the j-th column vector are orthogonal is expressed by the following equation (16) that the inner product of the complex vectors is zero.

The above equation transformation uses the formula of the sum of geometric progressions. Since this last condition is sufficient if the numerator is zero under the condition that the denominator is not zero, the condition that the term in the parentheses of exp of the numerator is an integral multiple of 2πi is conditional expression (17) below Led. In the following formulas, N is described as the original number of antennas N _{MT -Ant} .

The constant K ₁ of the equation (17) is an integer which is not a multiple of the number of antennas N _{MT -Ant} of the terminal station device 60. Here, as shown in FIG. 24, it is assumed that base station apparatus antenna #j on the base station apparatus 70 side has displacement d _{j in} the horizontal direction from the front of terminal station apparatus antenna # 1 on the terminal station apparatus 60 side. The difference between the antennas #i and #j is Δd _ij . The distance between the base station apparatus 70 and the terminal station apparatus 60 is L, and L / d is multiplied to both sides of the first equation of Expression (17). Distance slightly different, but if the distance L is sufficiently larger than the displacement d _j and L ≒ L _j approximation between the base station apparatus antenna # 1 of the base station apparatus antenna and the terminal station device 60 of the base station apparatus 70 It will be possible.

That is, with respect to the number of antennas _{N MT-Ant} terminal station _{60, N MT-Ant} to integer _{K 2} not be zero at integer multiples, the interval d of the antenna elements of the terminal station 60, terminal station 60 and the base With respect to the distance L of the station device 70 and the wavelength λ of the signal wave of wireless communication, the distance between any two antenna elements may be set to be the distance satisfying the equation (18). If this condition is geometrically interpreted, the condition can be easily realized, for example, under the following condition. For example, as the simplest condition, an arbitrary offset is allowed in the linear direction on a straight line whose distance from the linear station on the terminal station 60 side is L and away from the linear station, and N at λL / (N _MT -Ant d) intervals. _The point of the _MT-Ant point may be set linearly, the M point may be selected from the N _MT-Ant points, and the M antenna elements of the base station apparatus 70 may be arranged. This means that any two integers are selected from among consecutive N _{MT -Ant} integers, and their absolute value becomes (N _{MT -Ant} -1) or less whenever K is a difference, and K ₂ is N _MT It utilizes that it can avoid becoming an integral multiple of _Ant . In addition, it is possible to select the antenna installation point of the base station apparatus from other wider conditions by searching and setting an arrangement in which the difference between any two individual integers is not an integer multiple of N _MT-Ant. It is.

As shown in FIG. 23, when the antenna element 312 of the terminal station device 302 is miniaturized, the number N _MT-Ant of antenna elements of the terminal station device 302 is increased accordingly, while the antenna element of the base station device 306 is generally Since the number M is set to the upper limit of the assumed number of spatial multiplexing, it is assumed that the value of M is smaller than the number of antenna elements N _MT -Ant of the terminal station device 306. That is, when N _{MT -Ant} > M, the M antennas of the base station apparatus 306 need not be equally spaced even under the simplest conditions described above, and intermittently from among the above N _{MT -Ant} points. The arrangement position of the antenna element may be set.

  Although the actual number of antenna elements of the base station apparatus 303 is 100 in the case of FIG. 10, it can be regarded as four virtual antenna elements by grouping into 25 units. M should be considered to be 4. Moreover, although the approximation with very high accuracy is performed until derivation | leading-out of Formula (17), the approximation used in Formula (18) has a little low precision. However, although it depends on the setting of the parameters, if the distance between the antenna elements of the base station apparatus 70 in equation (18) is temporarily about 1 m, even if there is an error of several% of about several cm, it is almost orthogonal. There is no difference in things. Although the related art according to the present invention is the same, basically, even if there is an interference component between a plurality of virtual transmission paths on the receiving side, it is possible to suppress the interference by signal processing on the receiving side, If such signal processing is assumed, the loss can be minimized by making the state almost orthogonal to the last, so the approximation accuracy of equation (18) has no significant influence on the system operation.

  If such properties are taken into consideration, if each grouped antenna element group shown in FIG. 10 is regarded as one virtual antenna, that central point of the physically spread multi-element antenna is virtually set. Assuming that the physical position of the dynamic antenna and installing the plurality of antenna element groups in the above-described antenna arrangement, using a weight vector represented by the first singular vector, a plurality of signal sequences with desired characteristics are obtained. It becomes possible to transmit by space multiplexing.

In the above description, although the antenna element on the base station apparatus side and the antenna element on the terminal station apparatus side face each other and face each other as shown in FIG. As shown in FIG. 25, it is assumed that there is no facing relationship. This is due to the restriction on the installation places of the base station apparatus 306 and the terminal station apparatus 302. In such a case, the desired effect can be derived by converting the parameters slightly. In FIG. 25, when the terminal station apparatus 302 is viewed from the base station apparatus 306, the terminal station apparatus 302 exists in a direction shifted by an angle θ from the front, and when the base station apparatus 306 is viewed from the terminal station apparatus 302. The base station device 306 exists in a direction deviated from the front by an angle θ ′. In this case, the distance D ₁ between the parabola antennas 307-1 and 307-4 of the base station apparatus 306 can be seen from the terminal station apparatus 302 in a state of being narrowed to D ₁ ′ (= D ₁ cos θ). Similarly, the width D ₂ of the linear array 312 of the terminal station device 302 can be seen from the base station device 306 in a narrowed state to D ₂ ′ (= D ₂ cos θ ′). In other words, it can be understood that the antenna element distance d is converted to dcosθ × cosθ ′ times. Assuming that the distance between the terminal station apparatus 302 and the vicinity of the approximate center of gravity of the parabolic antennas 307-1 to 307-4 of the base station apparatus 306 is L, after performing these conversions, optimum antenna arrangement using the above-mentioned conditional expression The condition of can be calculated. That is, the base station apparatus 70 virtually projects each linear array on an axis orthogonal to the straight line in the line-of-sight direction. Similarly, the terminal station device 60 virtually projects each linear array on an axis orthogonal to the straight line in the line-of-sight direction. The d of the equation (18) is converted to d cos θ × cos θ ′ based on the virtually projected spacing of the on-axis antenna elements. Based on the spacing of the virtually projected on-axis antenna elements, d in equation (18) is converted by a conversion device or a person.

  Incidentally, although the distance between the terminal station apparatus 302 and the vicinity of the approximate center of gravity of the parabolic antennas 307-1 to 307-4 of the base station apparatus 306 is L in FIGS. 23 and 25, the exact distances of the individual antenna elements are common. Rather than the distance L, each will have an error. However, as understood from the use of approximation in the middle stage of the calculation of equation (18), a certain degree of error is also acceptable for the distance L at this point, and as shown in FIG. The distance between the elements (the distance between two straight lines of the antenna elements arranged in parallel straight lines) may be used, or as shown in FIG. 25, the distance may be approximately the center of gravity of the antenna elements. Thus, the distance L may be treated as an approximate value or an approximate value.

  In the description of FIG. 23 and FIG. 24 in the present description, the case where the terminal station apparatus is configured by a linear array is shown as a typical example. In this feature, parabola antennas 307-1 to 307-4 or 310-1 to 310-M (corresponding to antenna element groups 304-1 to 304-4 in FIG. 10) on the base station apparatus side are disposed on a straight line Similarly, the antenna elements on the terminal station side are arranged in a linear array on a straight line. In the calculation of the orthogonalization condition described above, the two straight lines are described as being in a parallel relationship. Specifically, assuming a horizontal axis parallel to the wall of the building, for example, on the wall of the building or on the roof of the building, a plurality of first signal processing units and antenna elements (groups) 307 along the horizontal axis. It is preferable to arrange the linear array of the terminal station apparatus also on a horizontal axis parallel to the wall surface of the opposite building separated from the road when the No.-1 to 307-4 are installed. Here, a vertical axis orthogonal to the horizontal axis on the terminal station side is set, and a grid parallel to the horizontal axis and the vertical axis is assumed, and the linear array of the terminal station described above is N in the vertical direction. Consider the case of using a stacked square grid array. At this time, the total number of antenna elements of the terminal station apparatus becomes N × N ′ elements. However, looking at the antenna elements (groups) 307-1 to 307-4 of the plurality of first signal processing units of the base station apparatus from this terminal station apparatus, although there are angular differences in the horizontal direction, they are perpendicular. As there is no difference between the antenna element (groups) 307-1 to 307-4 with respect to the elevation angle of the direction, each of the N 'stages of the above-mentioned square lattice array is not regarded as an independent antenna element, and is substantially vertical. It is understood that N 'elements arranged in a direction behave equivalently as one virtual antenna element, and the virtual antenna elements are arranged in a linear array on the horizontal axis in N elements. In fact, this effect is also confirmed in simulation evaluation, and the antenna element of the terminal station apparatus is parallel to the axis connecting the antenna element (groups) 307-1 to 307-4 on the base station apparatus side. When arranging an N × N ′ element in a lattice formed of an axis and an axis orthogonal to the axis, the N × N ′ elements are parallel to the axis connecting antenna elements (groups) 307-1 to 307-4 on the base station apparatus side. Assuming that the on-axis N element is a linear array of the element intervals of the N elements, the element interval of the antenna elements (groups) 307-1 to 307-4 on the base station apparatus side can be optimized by applying equation (12). good. Naturally, when the antenna elements (groups) 307-1 to 307-4 on the base station apparatus side are vertically aligned with the wall of the building, etc., the antenna elements on the terminal station apparatus side are also N elements in the vertical direction. Equation (12) may be applied by disposing N ′ elements in the horizontal direction in a lattice and regarding it as a linear array of equivalent N elements aligned in the vertical direction. Furthermore, although the antenna arrangement on the terminal station side has been described as a square lattice array here, the antenna arrangement need not necessarily be a square lattice, and the element spacing in the horizontal direction and the vertical direction may be different in a rectangular shape. In this case, the antenna element of the equation (12) is the spacing of the antenna elements arranged on the axis on the terminal station side parallel to the axis on which the antenna elements (groups) 307-1 to 307-4 on the base station side are aligned. It may be calculated as the interval d.

As described above, the related-art wireless communication system 53 according to the present invention includes the base station device 306 (first wireless station device) and the terminal station device 302 (second wireless station device). The base station apparatus 306 includes antenna elements (parabola antennas) 307-1 to 307-4, and the terminal station apparatus 302 includes a terminal station apparatus antenna element group 312. The plurality of parabola antennas (antenna elements) 307-1 to 307-4 of the base station apparatus 306 have a distance Δd _mn between the m-th element and the n-th element, as shown in equation (18), and a terminal station apparatus 302 based on the distance L between the base station 306 and the base station 306, the wavelength λ of the signal wave of wireless communication, the number of antennas N _MT-Ant of the terminal station 302, and the spacing d of the antenna elements of the terminal station 302 Ru. The parabolic antennas 307-1 to 307-4 are, for example, each a single high gain antenna element (single antenna element). The high gain antenna element is, for example, a parabolic antenna 307. The parabolic antennas 307-1 to 307-4 may be antenna element groups instead of a single high gain antenna element. When using the antenna element group in this manner, the base station apparatus 306 may be the base station apparatus 303 shown in FIG. 10 and the base station apparatus 17 in FIG. The base station apparatus 70 in FIG. 11 includes a plurality of first transmission signal processing units 181, a plurality of first reception signal processing units 185, a second transmission signal processing unit 71, and a second reception signal processing unit 75. And. The plurality of first transmission signal processing units 181 have a plurality of antenna elements 819. The plurality of first reception signal processors 185 have a plurality of antenna elements 851. The second transmission signal processing unit 71 performs signal processing of wireless communication associated with the plurality of first transmission signal processing units 181. The second received signal processing unit 75 performs signal processing of wireless communication associated with the plurality of first received signal processing units 185. The terminal station device 60 includes a plurality of antenna elements 819, a plurality of antenna elements 851, a transmission unit 61, and a reception unit 65. The transmission unit 61 performs wireless communication with the plurality of first reception signal processing units 185 via the plurality of antenna elements 819. The receiving unit 65 performs wireless communication with the plurality of first transmission signal processing units 181 via the plurality of antenna elements 851.

  That is, the distance L between the antenna elements or the distance between the antenna element groups is the distance L between the base station device 306 (first wireless station device) and the terminal station device 302 (second wireless station device), and the signal wave of wireless communication And the number N of linear array antenna elements constituting the second antenna element group or the number N of antenna elements in either the vertical direction or the horizontal direction arranged in a lattice, and the second antenna element Each single antenna element constituting the plurality of first antenna groups or an integral multiple of the value calculated based on the spacing d of either the vertical direction or the horizontal direction of the antenna elements constituting the group Antenna element groups are arranged.

  Accordingly, the base station apparatus 306 or 70, the terminal station apparatus 302 or 60, the wireless communication system 53 or 50, and the antenna element arrangement method according to the related art according to the present invention can transmit capacity by MIMO in an environment where line of sight environment dominates. It is possible to increase The base station apparatus 306 or 70, the terminal station apparatus 302 or 60, the wireless communication system 53 or 50, and the antenna element arrangement method according to the related art according to the present invention transmit a plurality of signal sequences spatially multiplexed and transmitted with desired characteristics. It becomes possible. The base station apparatus 306 or 70, the terminal station apparatus 302 or 60, the wireless communication system 53 or 50, and the antenna element arrangement method according to the related art according to the present invention can improve SIR characteristics. The base station apparatus 306 or 70, the terminal station apparatus 302 or 60, the wireless communication system 53 or 50, and the antenna element arrangement method of the related art according to the present invention can realize higher spatial multiplexing.

  The base station apparatus 306 or 70, the terminal station apparatus 302 or 60, the wireless communication system 53 or 50, and the antenna element arrangement method according to the related art according to the present invention are arranged on the base station apparatus 306 or 70 side in an environment dominated by line of sight. In the MIMO channels of the plurality of parabola antennas 307 and the plurality of element antennas on the terminal station device 302 or 60 side, antenna installation conditions for orthogonalizing each channel are defined. However, here the conditions for mounting a parabola antenna on the base station side are shown to simplify the discussion, but it goes without saying that a high directivity antenna other than the parabola antenna is used, and furthermore, the base station side has multiple antenna elements Even in the case of using the first signal processing unit as shown in FIG. 10 configured as shown in FIG. 10, it is possible to generally achieve orthogonalization between the respective transmission paths under the same conditions. This makes it possible to improve the communication quality on the transmission path and to increase the transmission capacity.

(Problems when applying the related technology of the present invention to an access system)
In the related art of the present invention, a plurality of first signal processing units are mounted in a plurality, and while each antenna element group is formed to be extremely small, by arranging them physically apart, a base station as a whole is obtained. A large-scale array is configured on the apparatus side, and wireless transmission is performed between each of the first signal processing units and the terminal station apparatus using a plurality of virtual transmission paths corresponding to the first singular value in parallel. Regarding the arrangement of the first signal processing unit of the base station apparatus at this time, as shown in the above-mentioned “Antenna arrangement condition for orthogonalization of line-of-sight MIMO transmission”, a base station such as use as an entrance line When both the device and the terminal station device are fixedly installed, the frequency (wavelength), the distance between the base station device and the terminal station device, the antenna element spacing of the terminal station device, so as to satisfy the equation (18) It is possible to optimize the number of antenna elements of the terminal station apparatus (the number of vertical or horizontal elements in the case of two-dimensional arrangement).

  However, in the case of the access system, the terminal station apparatus involves movement, and there is almost no case where both are always in the facing relationship, and furthermore, the relative positional relationship and direction change with time. In the most extreme example, when the terminal station apparatus comprises a linear array and the base station apparatus comprises a first signal processing unit linearly arranged, the respective linear antenna arrangements substantially face each other in parallel. The communication environment differs greatly between the case and the case where the respective linear antenna arrangements are orthogonal. When the antenna arrangement on each straight line is orthogonal, for example, the arrangement of the terminal station apparatus is rotated by 90 degrees, and the straight line in which the linear array of the terminal station apparatus is aligned and the straight line in which the first signal processing unit of the base station apparatus is aligned It is a case where it is in a twisted positional relationship.

  If the respective linear antenna arrangements are substantially facing each other in parallel, the distance between the base station apparatus and the terminal station apparatus is within a certain range from the ground height where the antenna of the base station apparatus is installed. It can be roughly estimated. By this, it is possible to secure a certain degree of suboptimal conditions without going to complete optimization. However, in the case where the straight line in which the respective antennas are arranged has a twisted orthogonal relationship, the correlation between the respective antenna elements becomes very strong, which is not suitable for spatial multiplexing. In other words, in this twisted state, a straight line parallel to a straight line on which the first signal processing unit of the base station apparatus is arranged is drawn on the terminal station apparatus side, and each antenna element of the terminal station apparatus It can be understood that, when projected, the projection points are concentrated at a very narrow place, so that the antenna element spacing is equivalently made very narrow and, as a result, the antenna correlation is enhanced.

  As a method for solving such a problem, it is conceivable to assemble the antenna elements on the terminal station apparatus side into a two-dimensional grid array. Thereby, a straight line parallel to a straight line in which the first signal processing units of the base station apparatus are arranged is drawn, and even when each antenna element of the terminal station apparatus is projected on the straight line, a certain degree of spatial spread is expected. Can. However, for example, when a smartphone or the like is assumed as the terminal station apparatus, the monitor screen of the smartphone usually faces upward when the user holds the smartphone in hand. Therefore, in order to efficiently utilize the line-of-sight wave (a direct wave without reflection) from the base station apparatus, many antenna elements must be arranged on the same side as the monitor screen of the smartphone. However, it is difficult to arrange the antenna element on the liquid crystal screen, and in practice, there is a large restriction on the arrangement, for example, the antenna element must be arranged one-dimensionally at the edge portion around the liquid crystal screen.

  FIG. 26 is a diagram showing an example of the antenna arrangement implemented in the terminal station apparatus in the related art of the present invention. In the figure, the code | symbol 501 represents a terminal | end station apparatus (smart phone), and the code | symbol 502-1-502-4 represent an antenna element. In the figure, an example in which four antenna elements are provided is shown, but for example, if the center frequency of the carrier wave is 20 GHz, the wavelength is 1.5 cm, and nine antenna elements in a linear array at half wavelength intervals. The length required for placement is approximately 6 cm. The distance between the antenna elements 502-1 and 502-4 in the figure is the maximum value of the antenna aperture length, which is 6 cm when nine antenna elements are arranged. Considering the width of a smartphone that fits in one hand, it is difficult to assume an antenna aperture longer than this.

  FIG. 27 is a diagram showing a form in which the user holds and uses the terminal station apparatus. When the base station apparatus is disposed at a relatively high position, radio waves come from above the terminal station apparatus 501 as shown in the figure. FIG. 28 is a diagram showing a case where the first signal processing unit of the base station apparatus is linearly arranged at a high place such as a building wall surface in the related art of the present invention. In the figure, reference numerals 501-1 to 501-2 denote terminal stations, reference numerals 511-1 to 511-5 denote first signal processing units (and array antennas), and reference numeral 515 denotes a service area. A service area 515 extends below the first signal processing units 511-1 to 511-5 linearly arranged on the building wall, and a plurality of terminal station devices 501-1 to 501-2 exist in the service area 515. As shown in FIG. 27, the user holds the terminal station devices 501-1 to 501-2 with the side on which the antenna element is installed (that is, the liquid crystal screen side) facing upward.

  FIG. 29 is a diagram showing the relationship between the arrangement of antenna elements of the terminal station apparatus and the arrangement of the first signal processing unit. In the figure, reference numerals 501-1 to 501-2 denote terminal stations, reference numeral 510 denotes a building wall, and reference numerals 511-1 to 511-5 denote first signal processing units (and array antennas of the base station). , 512-1 and 512-2 indicate antenna elements, 513-1 and 513 indicate directions in which the antenna elements of the terminal station apparatus are arranged, and 514 indicates a first signal of the base station apparatus. Indicates the direction in which the processing units are arranged. For example, as shown in FIG. 28, the signals transmitted downward from the first signal processing units 511-1 to 511-5 installed on the building wall surface have the antenna surface facing upward as shown in FIG. The terminal station device 501 held in the state will receive a signal. At this time, the direction in which the user holds the terminal station device 501, that is, the direction of the terminal station device 501 may have various angles.

  For example, in the terminal station device 501-1 in FIG. 29, the direction 513-1 in which the antenna elements 512-1 are arranged is parallel to the direction 514 in which the first signal processing units are arranged. With regard to the terminal station device 501-1, the width at which the antenna element 512-1 is disposed becomes the antenna aperture length as it is viewed from the base station device. However, with regard to the terminal station device 501-2 in FIG. 29, the direction 513-2 in which the antenna elements 512-2 are arranged is orthogonal to the direction 514 in which the first signal processing units are arranged. As for the terminal station device 501-2, as viewed from the base station device, a point obtained by projecting the plurality of antenna elements 512-2 on an axis parallel to the direction 514 in which the first signal processing units 511 are arranged appears as almost one point. The width is extremely narrow as the equivalent antenna aperture length.

  As described above, even in the terminal station apparatus according to the related art of the present invention, when the alignment of the transmitting antenna element and the receiving antenna element does not face each other, the antenna aperture is reduced. The orientation of the terminal station device 501-2 in which each array of antenna elements is orthogonal is the worst case where the antenna aperture is the shortest. At this time, in the antenna element 512-2, the correlation of the signals from the first signal processing units 511-1 to 511-5 is increased, and signal separation can not be performed by signal processing, that is, spatial multiplexing transmission becomes difficult. In addition, changing the direction of the terminal station device (the standing position of the user) and using it while communicating so that the antenna element on the transmitting side and the antenna element on the receiving side are directly opposed from the viewpoint of user operability It is not realistic.

  On the other hand, if the antenna elements can be two-dimensionally arranged in a square array on the upper surface of the terminal station apparatus, the reduction of the antenna aperture can be reduced. However, it is difficult to arrange the antenna element on the liquid crystal screen (lower layer side of the liquid crystal) of the smartphone, and in fact, as shown in FIG. 26, the antenna at the edge portion around the liquid crystal screen in the housing of the smartphone There is no choice but to arrange the elements.

First Embodiment of the Present Invention
FIG. 30 is a diagram showing a configuration example of the terminal station device 600A in the first embodiment according to the present invention. The terminal station apparatus 600A in the first embodiment performs MIMO transmission with a base station apparatus provided with at least one antenna array. The base station apparatus is, for example, the base station apparatus 303 or the base station apparatus 70 described with reference to FIGS. 9 to 13. The terminal station device 600A includes a two-dimensional array antenna 610. The two-dimensional array antenna 610 includes an antenna substrate 611 and a plurality of antenna elements 612. The plurality of antenna elements 612 are arranged in a matrix on one main surface of the antenna substrate 611 to form a two-dimensional array. The shape of the main surface of the antenna substrate 611 on which the plurality of antenna elements 612 are arranged is rectangular. The antenna substrate 611 is attached to the housing 601 of the terminal station device 600A via hinge portions 613-1 and 613-2 provided along one side of the main surface of the antenna substrate 611. The antenna substrate 611 is attached to the housing 601 so as to rotate around hinge portions 613-1 and 613-2.

  The thickness of the casing 601 of the terminal station device 600A is thinner than the longitudinal and lateral lengths of the casing 601, and the casing 601 has a plate-like shape having a certain thickness. On one main surface of the housing 601, a touch panel display 602 used when the user operates the terminal station device 600A is provided. The antenna substrate 611 rotates about the hinge portions 613-1 and 613-2, whereby the main surface on which the plurality of antenna elements 612 are arranged and the display 602 face in the same direction, and the main surface of the antenna substrate 611 The main surface of the antenna substrate 611 and the display 602 pass through the position (FIG. 30B) where the main surface of the antenna substrate 611 and the display 602 cross at right angles from the position (FIG. 30A) where the In the opposite direction, the antenna substrate 611 and the display 602 are attached to the housing 601 so as to rotate through 180 degrees to the facing position (FIG. 30C). The angle at which the antenna substrate 611 rotates about the hinge portions 613-1 and 613-2 may be 180 degrees or more. In addition, when the main surface of the antenna substrate 611 and the display 602 face each other in the opposite direction, as shown in FIG. Housed in

  The plurality of antenna elements 612 are connected to the transmission unit 61 and the reception unit 65 (FIG. 14) provided in the housing 601. Signal lines connecting the plurality of antenna elements 612 to the transmitter 61 and the receiver 65 are provided via hinge portions 613-1 and 613-2. When the user uses the terminal station device 600A for communication, the antenna substrate 611 is rotated, and the two-dimensional array antenna 610 is moved to the upward-facing position as in the display 602 as shown in FIG. be able to. As a result, it becomes easy to make the antenna array of the base station apparatus provided at a high place of a building or other building face the two-dimensional array antenna 620 of the terminal station apparatus 600A face-to-face, and received by each antenna element 622 An increase in correlation between signals can be reduced, and transmission capacity can be increased in a wireless communication system that performs MIMO transmission in a communication environment in which a sight wave is dominant.

  In addition, since the plurality of antenna elements 612 are arranged in a matrix, the antenna aperture length of the two-dimensional array antenna 610, regardless of which direction the terminal station device 600A faces with respect to the antenna array of the base station device. Can be prevented from becoming narrow. Further, since the antenna substrate 611 can be accommodated in the housing 601, the two-dimensional array antenna 610 can be provided in the terminal station device 600A while suppressing an increase in size of the terminal station device 600A.

Second Embodiment of the Present Invention
FIG. 31 is a view showing a configuration example of a terminal station device 600B in the second embodiment according to the present invention. The terminal station device 600B in the second embodiment performs MIMO transmission with a base station device including at least one antenna array, as in the terminal station device 600A in the first embodiment. Terminal station apparatus 600 B includes a two-dimensional array antenna 620. The two-dimensional array antenna 620 includes an antenna substrate 621 and a plurality of antenna elements 622. The plurality of antenna elements 622 are arranged in a matrix on one main surface of the antenna substrate 621 to form a two-dimensional array. The main surface of the antenna substrate 621 on which the plurality of antenna elements 622 are disposed has a rectangular shape. Grooves 623-1 and 623-2 are formed on the elongated surfaces located on both sides of the main surface of the antenna substrate 621 in the longitudinal direction of the surfaces.

  The thickness of the case 603 of the terminal station device 600B is thinner than the length in the longitudinal direction and the lateral direction of the case 603, and the case 603 has a plate-like shape having a certain thickness. On one of the main surfaces of the housing 603, a touch panel display 602 used when the user operates the terminal station device 600B is provided. Inside the housing 603, guide portions 605-1 and 605-2 for guiding the movement of the antenna substrate 621 are provided at positions facing the grooves 623-1 and 623-2 of the antenna substrate 621. The guide portions 605-1 and 605-2 are formed as, for example, convex portions having a shape corresponding to the shape of the grooves 623-1 and 623-2. The guide substrate 605-1 and 605-2 guide the movement of the antenna substrate 621 along the grooves 623-1 and 623-2, so that the antenna substrate 621 accommodated in the housing 603 is a main surface of the housing 603. And the surface on which the plurality of antenna elements 622 are disposed can be exposed to the side on which the display 602 is provided.

  In the terminal station device 600B, the antenna substrate 621 is mounted on the housing 603 by having a slide mechanism for guiding the movement of the antenna substrate 621 along the grooves 623-1 and 623-2 by the guide portions 605-1 and 605-2. From the accommodated state (FIG. 31C), the antenna substrate 621 is moved parallel to the main surface of the housing 603 (FIG. 31B), and arranged in a matrix on the main surface of the antenna substrate 621. The plurality of antenna elements 622 can be moved to the same side as the display 602 (FIG. 31A). The direction in which the antenna substrate 621 moves is a direction perpendicular to the thickness direction of the housing 603, for example, a direction parallel to the longitudinal direction or the horizontal direction of the housing 603.

  The plurality of antenna elements 622 are connected to the transmitting unit 61 and the receiving unit 65 (FIG. 14) provided in the housing 603. A plurality of antenna elements 622 are signal lines connected via contacts provided in the vicinity of the guide portions 605-1 and 605-2, or signal lines and flexible printed boards that can expand and contract due to bending or the like in the housing 603. Are electrically connected to the transmitter 61 and the receiver 65. When the user uses the terminal station device 600B for communication, the antenna substrate 621 is pulled out, and as shown in FIG. 31A, a plurality of antennas with the two-dimensional array antenna 620 directed upward as in the display 602. The element 622 can be moved to the exposed position. As a result, it becomes easy to make the antenna array of the base station apparatus provided at the height of a building or other building face the two-dimensional array antenna 620 of the terminal station apparatus 600 B face-to-face, and received by each antenna element 622 An increase in correlation between signals can be reduced, and transmission capacity can be increased in a wireless communication system that performs MIMO transmission in a communication environment in which a sight wave is dominant.

  In addition, since the plurality of antenna elements 622 are arranged in a matrix, the antenna aperture length of the two-dimensional array antenna 620 can be obtained regardless of which direction the terminal station device 600B is directed to the antenna array of the base station device. Can be prevented from becoming narrow. Further, since the antenna substrate 621 can be accommodated in the housing 603, the two-dimensional array antenna 620 can be provided in the terminal station device 600B while suppressing an increase in size of the terminal station device 600B.

  Note that when the antenna substrate 621 is housed in the housing 603 as shown in FIG. 31C, or as shown in FIG. 31B, some of the plurality of antenna elements 622 are housing 603. When in the inside, the terminal station device 600B may not transmit a signal from the two-dimensional array antenna 620. Accordingly, the wireless signal transmitted from the two-dimensional array antenna 620 can be prevented from being absorbed by the housing 603 or an element or the like provided in the housing 603, and efficient transmission can be performed.

  Also, as a slide mechanism for guiding the movement of the antenna substrate 621, the grooves 623-1 and 623-2 provided on the antenna substrate 621 and the convex portions of the guide portions 604-1 and 604-2 provided on the housing 603. However, as long as it is a slide mechanism that moves the antenna substrate 621 in parallel, another configuration may be used.

Third Embodiment of the Present Invention
FIG. 32 is a view showing a configuration example of a terminal station device 600C in the third embodiment according to the present invention. Similar to the terminal station device 600A of the first embodiment, the terminal station device 600C in the third embodiment performs MIMO transmission with a base station device provided with at least one antenna array. The terminal station device 600C includes a two-dimensional array antenna 630. The two-dimensional array antenna 630 includes an antenna substrate 631 and a plurality of antenna elements 632. The plurality of antenna elements 632 are arranged in a matrix on one main surface of the antenna substrate 631 to form a two-dimensional array. The main surface of the antenna substrate 631 on which the plurality of antenna elements 632 are disposed has a fan-like shape. The antenna substrate 631 is attached to the housing 607 of the terminal station device 600C via the hinge portion 633 via the hinge portion 633 attached to the vicinity of the main portion where the two linear portions of the antenna substrate 631 intersect. . The antenna substrate 631 is attached to the housing 607 so as to rotate with the direction of the main surface of the antenna substrate 631 fixed with the hinge portion 633 as an axis.

  The thickness of the housing 607 of the terminal station device 600C is thinner than the length in the vertical direction and the horizontal direction of the housing 607, like the housing 601 etc., and the housing 607 is a plate having a certain thickness. It has the shape of On one of the main surfaces of the housing 607, a touch panel display 602 used when the user operates the terminal station device 600C is provided. The antenna substrate 631 rotates about a hinge portion 633 attached near the corner of the main surface of the housing 607. In the antenna substrate 631, the main surface on which the plurality of antenna elements 632 are arranged and the display 602 face in the same direction, and the antenna from the position where the main surface of the antenna substrate 611 and the display 602 are arranged (FIG. 32A) A position where the antenna substrate 631 is accommodated in the housing 607 (see FIG. 32B) through a position where a part of the plurality of antenna elements 632 disposed on the main surface of the substrate 631 is hidden in the housing 607 (FIG. It is attached to the housing 607 so as to rotate through 90 degrees up to 32 (C).

  The plurality of antenna elements 632 are connected to the transmission unit 61 and the reception unit 65 (FIG. 14) provided in the housing 607. The plurality of antenna elements 632 connect the transmitting unit 61 and the receiving unit 65 by a signal line connected via the hinge portion 633 or a signal line or flexible printed circuit that can be expanded or contracted by bending in the housing 607 or the like. It is done. When the user uses the terminal station device 600C for communication, the antenna substrate 631 is rotated and pulled out, and the two-dimensional array antenna 630 is directed upward as in the display 602, as shown in FIG. It can be exposed. As a result, it becomes easy to make the antenna array of the base station apparatus provided at a high place of a building or other building face the two-dimensional array antenna 630 of the terminal station apparatus 600 C face-to-face. An increase in correlation between signals can be reduced, and transmission capacity can be increased in a wireless communication system that performs MIMO transmission in a communication environment in which a sight wave is dominant.

  When the antenna substrate 631 is accommodated in the housing 607 as shown in FIG. 32C, or as shown in FIG. 32B, a part of the plurality of antenna elements 632 is a housing 607. When in the inside, the terminal station apparatus 600C may not transmit a signal from the two-dimensional array antenna 630. Accordingly, the wireless signal transmitted from the two-dimensional array antenna 630 can be prevented from being absorbed by the housing 607 or an element or the like provided in the housing 607, and efficient transmission can be performed.

  Further, in FIG. 32, the hinge portion 633 is attached to the vicinity of the corner of the main surface of the housing 607. However, the antenna substrate 631 is rotated while maintaining the parallel state to the main surface of the housing 607. The hinge portion 633 may be attached to any position of the housing 607 as long as it can be positioned.

Fourth Embodiment of the Present Invention
FIG. 33 is a diagram showing a configuration example of a terminal station device 600D in the fourth embodiment according to the present invention. The terminal station device 600D in the fourth embodiment performs MIMO transmission with a base station device provided with at least one antenna array, similarly to the terminal station device 600A in the first embodiment. The terminal station device 600D includes a linear array antenna 640. The linear array antenna 640 includes an antenna substrate 641 and a plurality of antenna elements 642. The plurality of antenna elements 642 are linearly arranged on one main surface of the antenna substrate 641 to form a linear array. The shape of the main surface of the antenna substrate 641 on which the plurality of antenna elements 642 are arranged is an elongated rectangular shape. The antenna substrate 641 is attached to the housing 609 of the terminal station device 600D via a hinge portion 643 attached in the vicinity of one of the two end portions in the longitudinal direction of the antenna substrate 641. The antenna substrate 641 is attached to the housing 609 so as to rotate with the direction of the main surface of the antenna substrate 641 fixed with the hinge portion 643 as an axis (fulcrum).

  The thickness of the housing 609 of the terminal station device 600D is thinner than the length in the vertical direction and the horizontal direction of the housing 609 as in the housing 601 and the like, and the housing 609 has a plate-like thickness. It has the shape of On one of the main surfaces of the housing 609, a touch panel display 602 used when the user operates the terminal station device 600D is provided. The antenna substrate 641 rotates about a hinge portion 643 attached in the vicinity of a corner of the main surface of the housing 609. As shown in FIG. 33, the antenna substrate 641 is rotated about the hinge portion 643 from the position where it protrudes in the longitudinal direction of the housing 609 (FIG. 33A), and the longitudinal direction of the housing 609 and the antenna substrate 641 are The housing 609 is rotated to a position accommodated in the housing 609 through a position (FIG. 33B) in which the angle between the longitudinal direction and the target is any angle from 0 to 180 degrees. It is attached. The angle at which the antenna substrate 641 rotates about the hinge 643 may be 180 degrees or more.

  The plurality of antenna elements 642 are connected to the transmission unit 61 and the reception unit 65 (FIG. 14) provided in the housing 609. Signal lines connecting the plurality of antenna elements 642 to the transmitter 61 and the receiver 65 are provided via hinges 643. When the user uses the terminal station device 600D for communication, the antenna substrate 641 is rotated, and the linear array antenna 640 is directed upward similarly to the display 602 as shown in FIG. 33 (A) or FIG. 33 (B). It can be exposed at the position where it was. As a result, it becomes easy to make the antenna array of the base station apparatus provided at a high place of a building or other building face up against the linear array antenna 640 of the terminal station apparatus 600D, and the signals received by each antenna element 642 An increase in correlation between the two channels can be reduced, and transmission capacity can be increased in a wireless communication system that performs MIMO transmission in a communication environment in which a sight wave is dominant.

  Further, one of the features of the terminal station device 600D is that, as shown in FIG. 29, the antenna aperture length largely changes in accordance with the direction when the user holds the terminal station device 501 in hand. Since the direction of the linear array antenna 540 can be adjusted regardless of the direction of the station device 500D, a wide antenna aperture length can be secured.

  FIG. 34 is a diagram showing the relationship between the orientation of the linear array antenna 640 of the terminal station device 600D and the arrangement of the first signal processing unit 511 of the base station device. In the figure, reference numerals 500D-1 to 500D-3 denote terminal stations, reference numeral 510 denotes a building wall, and reference numerals 511-1 to 511-5 denote first signal processing units provided in the base station (and Array antenna, and reference numeral 514 indicates the direction in which the first signal processing units 511 of the base station apparatus are arranged, and reference numerals 533-1, 533-2, and 533-3 indicate the direction in which the linear array antennas of the terminal station apparatus 600D are arranged. Indicates For example, although the terminal station device 600D-1 is in a state where the user faces the building wall surface 510 side (first signal processing unit side), the linear array antenna is arranged in the direction 514 in which the first signal processing units 511 are arranged. By orienting in the parallel direction 533-1, the direction 514 in which the first signal processing units 511-1 to 511-5 are arranged is kept parallel to the direction 533-1 in which the antenna elements are arranged in the linear array antenna, A state in which the first signal processing unit 511 and the linear array antenna substantially face each other can be secured.

  In addition, although the terminal station device 600D-2 is in a state in which the user stands in a direction to look sideways on the building wall surface 510 side (the first signal processing unit side), the linear array antenna of the terminal station device 600D is directed 514 By keeping the direction 514 in which the first signal processing units 511-1 to 511-5 are lined in parallel with the direction 533-2 in which the linear array antennas are lined. A state in which the signal processing unit 511 and the linear array antenna substantially face each other can be secured. Furthermore, although the terminal station device 600D-3 is in a state where the user stands obliquely to the building wall 510 side (the first signal processing unit side), the linear array antenna is used as the first signal processing unit. By orienting in a direction 533-3 parallel to the direction 514 in which the lines 511 are arranged, the direction 514 in which the first signal processing units 511-1 to 511-5 are arranged is parallel to the direction 533-3 in which the antenna elements in the linear array antenna are arranged. It is possible to maintain a state where the first signal processing unit 511 and the linear array antenna substantially face each other.

  As shown in FIG. 26, when the antenna element is disposed at the edge of the periphery of the display of the smartphone (terminal station device), the antenna aperture length is large depending on the direction of the terminal station device when held by the user. As a result, as shown in FIG. 29, it may be difficult to carry out a large number of spatial multiplexing transmissions with the first signal processing unit 511, or a situation may occur where the communication becomes unstable. In contrast, as shown in FIG. 34, the terminal station apparatus 600D in the fourth embodiment stably rotates the antenna opening length of the linear array antenna 640 by rotating the antenna substrate 641 with respect to the housing 609. As a result, it is possible to ensure communication stability and increase the number of spatial multiplexing, and improve communication quality.

  In the above description, the antenna substrate 641 is described to allow only rotation (that is, rotation in a single plane) around one axis indicated by the hinge portion 643, but in general the hinge portion 643 It is also possible to extend the configuration of to increase the degree of freedom in the direction of rotation with multiple axes. In the simplest implementation, the hinge 643 may be realized by a combination of two hinges, one hinge may realize rotation in a plane, and the remaining hinges may allow movement out of this plane. Also, there are various ways of realizing such hinges, and any arbitrary way of realizing them may be used.

  As described above, the terminal station apparatus of each embodiment is a terminal station apparatus that performs MIMO transmission with a base station apparatus provided with a plurality of antenna elements or array antennas, and is movably attached to the housing and the housing And a plurality of antenna elements disposed on the main surface of the antenna substrate. That is, the terminal station apparatus has a configuration in which the antenna element can be arranged on the antenna substrate so as to face the first signal processing unit (and the array antenna) of the base station apparatus independently of the display surface of the terminal station apparatus. It is characterized by having. In the array antenna formed by the plurality of antenna elements, the antenna substrate is movable with respect to the housing, and therefore, the plurality of antenna elements or the array antenna of the base station apparatus can be used regardless of the orientation of the housing. A wireless communication system capable of securing a directly facing position, reducing an increase in correlation between signals received by each antenna element of a terminal station apparatus, and performing MIMO transmission in a communication environment in which a sight wave is dominant Transmission capacity can be increased. Furthermore, as described above, since there is no need to change the orientation of the terminal station case, it is possible to improve the operability at the time of user communication.

  In the terminal station apparatus of each embodiment, a cover covering the antenna element may be provided on the side of the antenna substrate on which the plurality of antenna elements are disposed, in order to protect the antenna element. The member as the cover is preferably made of a material that does not hinder the transmission and reception of radio waves.

[Supplementary matter of the embodiment according to the present invention and the related art]
In the following, some supplementary points regarding the embodiment according to the present invention and the related art will be described.

  First, in describing the embodiments of the present invention, the related techniques have been described in detail, and these related techniques are techniques corresponding to the environment that brings about the situation in which the embodiments of the present invention function most efficiently. Therefore, the effects of the embodiment of the present invention can not be expected unless the related art is applied simultaneously. That is, even in the case of using in a combined environment of technologies different from the related art, the application of the embodiment of the present invention makes it possible to widely secure the aperture length of the antenna without depending on the arrival direction of radio waves. As a result, it is possible to obtain the effects of the present invention.

  In addition to the antenna element shown in the embodiment of the present invention, a general terminal station apparatus mounts another antenna element at any place in the housing of the terminal station apparatus, and uses these together. Is also possible. Even in such a case, the antenna aperture length is surely expanded by the use of the antenna element shown in the embodiment of the present invention, and the effect of the present invention can be obtained as a result even if any signal processing is performed. It is possible. Therefore, the intended scope of the present invention should fall within the scope of the claims regardless of the application of the related art and the combination of other antenna elements.

  Similarly, it is also possible to mount a part of antenna elements on the back surface of the antenna base of each embodiment, and to use the antenna element on the back surface together with the antenna element on the front surface. However, for example, as shown in FIG. 28 and the like, the line of sight wave when the base station apparatus exists substantially upward as viewed from the terminal station apparatus is mainly on the surface of a smartphone or the like, that is, the side on which a liquid crystal monitor or the like is disposed. In order to arrive, when the antenna base is moved so that the antenna element shown in each embodiment is directed to the side where the liquid crystal monitor or the like is arranged, the effect of the good communication characteristics is suitable for transmitting and receiving signals using incoming waves. It will be obtained by the antenna element on the front side of the antenna base. For this reason, the antenna element on the back of the antenna base can produce only a limited effect, and the addition of such an additional antenna element should be included in the scope of the present invention.

Further, in the description of the related art applicable to each embodiment of the present invention, the antenna elements 851-1 to 851- (N'BS _-Ant ) on the reception side and the antenna elements 81819 to 819- (N on the transmission side) Although different numbers are assigned to each ' _BS-Ant ' and explanations are given individually, it goes without saying that antenna elements (851-1 to 851-) common to the transmitting system and the receiving system via TDD-SW etc. It is also possible to treat it as (N'BS _-Ant ) or 819-1 to 819- (N'BS _-Ant ). In particular, in the case of performing implicit feedback, it is essential to share antennas of the transmitting system and the receiving system, and TDD control in which uplink and downlink are switched in time is fundamental. The switching of the TDD-SW here is managed and controlled by the communication control circuit 120 and the like.

Also, the reception antenna element 851-1 to 851- (N'BS _-Ant ) for the base station apparatus and the transmission antenna element 812-1 to 819- (N'BS _-Ant ) and the reception for the terminal station apparatus and in the side of the antenna element 851-1~851- _{(N MT-Ant)} and the transmission side of the antenna element 819-1~819- _{(N MT-Ant),} a common number in order to simplify the description, respectively To explain. However, the requirements such as the antenna element size and directivity gain for the base station apparatus and the requirements such as the antenna element size and directivity gain of the terminal station apparatus generally do not match, and the functions are the same. Although the same number is given as the number, in actual operation, antenna elements having different conditions in terms of size, directivity gain, etc. may be used. The same holds true for the other circuits, and the description is made using common numbers for the sake of simplicity. For example, high power amplifiers 818-1 to 818-(N ' _BS-Ant and N _{MT- Ant),} a low noise amplifier 852-1~852- (N _'BS-Ant and _{N MT-Ant)} even in such similarly amplification factor of the amplifier, requirements such as power consumption, size and permissible heating value is generally coincident Although the same number is assigned as the number because the function is the same, the circuit of different conditions may be used in actual operation.

  Further, the transmission weight vector in the related art of the present invention means each column vector (or a part of column vectors) of the transmission weight matrix, and is a vector-described transmission weight focused on one of the signal sequences to be spatially multiplexed simultaneously. is there. Specifically, each column vector of the transmission weight matrix at the time of spatially multiplexing a plurality of signal sequences is a vector representation of weights (components of the transmission weight vector) focusing on a certain signal sequence among the plurality of signal sequences. In the process of generation of the entire transmission weight matrix based on the channel vector or channel matrix of the terminal station apparatus to be spatially multiplexed. Therefore, the generation of the transmission weight vector (and also when words such as "calculation", "determination", "multiplication", and "component" follow) is equivalent to the generation of the transmission weight matrix as a whole, in particular When considering a procedure for sequentially generating row vectors or column vectors of a matrix, it may be marked as "generation of transmission weight vector" in a sense equivalent to "generation of transmission weight matrix".

  Similarly, in the related art of the present invention, the reception weight vector means each row vector (or a part of row vectors) of the reception weight matrix, and vector notation focused on one of the spatially multiplexed signal sequences simultaneously It is a reception weight. Specifically, each row vector of the reception weight matrix when a plurality of signal sequences are spatially multiplexed is a vector representation of weights (components of the reception weight vector) focusing on a certain signal sequence among the plurality of signal sequences. In the process of generation of the entire reception weight matrix based on the channel vector or channel matrix of the spatially multiplexed terminal station apparatus. Therefore, the generation of the reception weight vector (and also when words such as "calculation", "determination", "multiplication", and "component" follow) is equivalent to the generation of the reception weight matrix as a whole, in particular When considering a procedure for sequentially generating row vectors or column vectors of a matrix, it may be marked as "generation of reception weight vector" in a meaning equivalent to "generation of reception weight matrix".

  Furthermore, “vectors” in various forms such as “transmission weight vector”, “reception weight vector”, “channel (information) vector”, “transmission signal vector”, and “reception signal vector” in the related art of the present invention These are all vectors that use "transmission weight", "reception weight", "channel (information)", "transmission signal" and "reception signal" as components corresponding to each antenna element. Even if there is no explicit mention of “vector” in each relevant art, it is clear that what constitutes them in the relevant art is those “vectors”, if necessary. Should be understood by supplementing these contents. Furthermore, "transmission signal" and "reception signal" in "reception signal vector" and "reception signal vector" are transmission or reception signals corresponding to each antenna element or based on each antenna element, and are actually transmitted and received. It may be a digitalized baseband (or intermediate frequency) signal instead of a radio frequency analog signal. This signal includes both a signal on the frequency axis and a sampling signal on the time axis. Therefore, although there is a part where explicit description is omitted in the description of the related art above, these signals are not only the signals transmitted and received on the radio frequency but also the signals transmitted and received on the radio frequency. Between the signals, some signal processing may be performed.

  Further, in the description of channel estimation in the related art of the present invention, in addition to the case of acquiring channel information by one channel estimation, the case of averaging a plurality of channel estimation results is also described. For example, considering the line gain by utilizing a large-scale antenna element, there is no problem if the line gain is insufficient in the line design between one antenna and one antenna, but the directivity by the large-scale antenna In order to gain the sex gain, appropriate transmit and receive weights are required, and the channel information required to calculate the transmit and receive weights is basically based on the channel estimation result between one antenna and one antenna. If the line gain is insufficient, the directivity gain can not be obtained thereafter. As a countermeasure for this, in Non-Patent Document 2 and the like, a training signal is received by a plurality of symbols, and the shortage of channel gain is compensated by averaging the received signals. As averaging of the plurality of estimation results, in the case where a periodic training signal continues over several symbols, a method of performing short-term averaging over several symbols utilizing the periodicity and discrete There is a method of performing long-time averaging in which channel estimation results performed at time are gathered for a plurality of times and averaging is performed. Here, in the case of short-time averaging, since a plurality of symbols to be averaged are continuous, it is considered that all symbol timings are preserved because of their periodicity. It was not necessary to treat it as a relative channel based on the complex phase. On the other hand, with regard to channel estimation results performed at discrete times, it is generally not necessary that the symbol timing be the same. Therefore, relative channel information is used to eliminate the influence associated with the error of the symbol timing. It was necessary to take a configuration to acquire and average. In this case, the complex phases of the channel information of the reference antenna element are all considered to be zero (ie, take real values). In calculation of these relative channel information, channel information of all antenna elements is multiplied by Exp (-jθ) by complex phase θ of the reference antenna, and channel information of all antenna elements is used as a reference It may be obtained by dividing by the channel information of the antenna element. Such utilization of relative channel information is generally essential for averaging channel estimation results with different symbol timings, but in the case where symbol timings are common, relative channel is generally used in calculating transmission / reception weights. There is no need to use information. It suffices to simply calculate the transmission / reception weight using the equation (1) or the equation (7) for the acquired channel information. However, even if the symbol timing is common, there is no problem even if the relative channel information is used, so sometimes the above description will be described as relative channel information or simple channel information. There is a case where it is used as it is. However, the difference is as described above, and it is not necessary to use relative channel information.

  In acquisition of channel information in the related art of the present invention, processing such as short time averaging and long time averaging is performed particularly when used in an entrance link etc. in channel estimation between one antenna and one antenna. It compensates for the lack of channel gain. However, in the case of the access system, the terminal station apparatus and the environment around it move and change with time, and therefore processing such as short time averaging and long time averaging can not be performed. However, if conventional techniques for performing channel estimation between one antenna and one antenna with various techniques with a predetermined accuracy are used, it is possible to obtain channel information in real time or feedback of channel information, In that case, it becomes possible to calculate necessary transmission / reception weights using the obtained relative channel information.

  Also, relative channel information can be treated as channel information obtained by correcting the complex phase with reference to the complex phase of the reference antenna, or the channel information of the antenna element as channel information of the antenna including the amplitude. Information may be divided. The amplitude of each piece of relative channel information has a meaning, for example, in the case of the reception weight of maximum ratio combination represented by equation (7), but in the case of the transmission / reception weight of equal gain combination represented by equation (1) do not have. Furthermore, in practice, in the line-of-sight environment, the deviation of the amplitude of each antenna is expected to be very limited, in which case there is no significant difference even if all are approximated with the same amplitude. In the first place, the absolute value of the transmit and receive weights has no significant meaning, and needs to be separately optimized to be an efficient value among the limited number of quantization bits, but it is related to the number of such quantization bits The discussion is completely different from the related art of the present invention, and optimization may be made among existing technologies. In that sense, the size (absolute value) of the transmit / receive weight vector as a vector does not have a special meaning here, and the transmit / receive weight vector multiplied by an arbitrary coefficient also has its statistical properties preserved here. It is explaining.

  Various signal processing can be simplified in the related art of the present invention by using the above relative channel information. On the other hand, in the conventional MIMO transmission technology, for example, the process of multiplying the reception weight matrix directly has been described as including the process of converting into a state suitable for signal detection. That is, even for SISO signals, for signal detection processing, the received signal is divided by the channel estimation result, and the signal point on the constellation where the I and Q axes are correctly set from the received signal subjected to channel distortion. Needed to be converted. In the related art of the present invention, the multiplication processing of transmission / reception weights performed in the first signal processing unit mainly aims at securing directivity gain and signal processing for rough signal separation, and thus transmission / reception The received signal is divided by the channel estimation result, as it is possible to treat many antenna elements as one virtual antenna element by multiplication of weights, and the I / Q axis is obtained from the received signal subjected to channel distortion. Does not include the process of converting into signal points on the constellation set correctly. However, on the reception side, processing such as signal detection can also be performed in the subsequent stage, and the same signal processing as the signal processing performed in conventional MIMO transmission or SISO transmission can be applied to these processing. is there. Particularly, in the reception system of the base station apparatus, these processes are performed in the second signal processing circuit.

  Also, when a training signal composed of limited subcarrier components is transmitted from different antenna elements on the transmitting station side without overlapping of subcarriers allocated by each antenna element, there is no overlap on the frequency axis The nuclear training signal is combined in space and received at the receiving station as a training signal containing more subcarrier components. In this sense, the receiving station side is different from the training signal transmitted by each antenna element on the transmitting side, but the training signal synthesized in space (referred to as “combined training signal”) is regarded as a normal training signal. It becomes possible to perform signal processing. Also in the case of using such a synthetic training signal, it is effective to convert channel information into relative channel information which is a relative value with respect to the antenna element serving as a reference.

  In the above description, although k (for example, the k-th frequency component) representing subcarriers is omitted for the sake of simplicity, and further, there is a case where the description regarding individual subcarriers is also omitted. The system assumed is a wide-band system, and all signal processing for channel information, transmission / reception weights, and further for transmit and receive signals, etc. is basically on the frequency axis, except for signal processing on the time axis, etc. And should be individually defined and processed for each subcarrier. Therefore, in order to simplify the description, in many descriptions, subscripts that explicitly represent subcarriers have been omitted. However, these descriptions are actually performed individually for each subcarrier, and in that case, the descriptions can be interpreted exactly if they are understood by adding subscripts representing the subcarriers. Inside each signal processing circuit, for example, signal processing up to the previous stage of IFFT processing on the transmission side (in the case of OFDM modulation as an example, interleaving of bit strings, mapping of signal points, modulation of signals, transmission weight vector The multiplication and the like are all performed for each subcarrier, and the signal processing after FFT processing on the reception side (also assuming the OFDM modulation method, multiplication of reception weight, signal detection processing, signal de- Mapping, deinterleaving, etc.) are all performed for each subcarrier.

  Also, in terms of circuit configuration, separate circuits may be provided for each subcarrier, or since the same processing is performed, processing is performed serially for each subcarrier, and the circuit is shared for subcarriers. It is also possible to Furthermore, a plurality of circuits may be prepared intermediately, the subcarrier may be divided appropriately, and the parallel processing may be performed serially by the plurality of circuits. These are stories that are common to all related technologies.

  Further, in the OFDM modulation scheme, all subcarriers are used for communication with the same terminal station apparatus, so the transmission / reception weights (averaged transmission / reception weight vector and real-time transmission / reception weight matrix) at that time are common to all subcarriers. The transmission and reception weights for the terminal station apparatus of the combination will be used. However, in OFDMA, assignments are made to different combinations of terminal stations in a patchwork manner on the time axis and the frequency axis, and therefore, they are assigned for each time (OFDM symbol) and frequency (subcarrier). It is necessary to use transmission / reception weights for the terminal station apparatus. However, except for the difference, OFDM and OFDMA can be processed in exactly the same way, and in the present specification, the explanation has been made focusing on OFDM, but the embodiment of the present invention is applied to OFDMA in exactly the same way. can do.

  In addition, although there are various operational variations regarding SC-FDE, received signal processing after signals transmitted from each antenna element are combined in space after multiplication by a transmission weight vector on the transmission side, and In each of the above configuration examples, the processing performed in the conventional SC-FDE can be applied as it is to any of the reception signal processing after the reception weight is multiplied on the reception side and the signals of the respective antenna elements are added and synthesized. Because of the configuration, it is applicable to all variations of SC-FDE. In this case, signal processing with a single carrier is performed instead of signal processing with the OFDM modulation scheme, and then, in the case of downlink, FFT processing is performed on the signal on the time axis of the single carrier, thereby each subcarrier. The following signal components may be generated, and these signal components may be regarded as the signal of each subcarrier generated by the OFDM modulation scheme and multiplied by the transmission weight vector generated by the related art of the present invention. Similarly, in the case of the uplink, the signal obtained by subjecting the received signal to FFT processing is treated in the same manner as in the case of the OFDM modulation scheme, and signal separation is performed by multiplying the reception weight vector generated according to the present invention. The subcarrier signal may be converted to a single carrier signal on the time axis by performing IFFT processing. As described above, although there is a difference between part of signal processing between the OFDM modulation method and SC-FDE, generation of transmission / reception weights and multiplication processing are common, and the embodiment of the present invention It is applicable.

  Also, in spatial multiplexing transmission, a plurality of series of signals are transmitted in parallel, but in the above related art, processing such as error correction performed on these signal series is independently performed for each signal series as an example. As described above, it goes without saying that the signal after error correction coding is serial / parallel converted at the transmitting side to separate into a signal sequence to be spatially multiplexed, and the signal before the error correction processing is performed on the receiving side. Parallel / serial conversion may be performed, and then error correction processing such as Viterbi decoding of one system may be performed. Furthermore, any error correction processing may be performed regardless of the essence of the related art of the present invention, including other variations. In this case, the exchange of signals between the MAC layer processing circuit and the second signal processing unit etc. is not performed in the space multiplex system, but, for example, information exchange is performed as a single system signal, and serial / A function corresponding to parallel conversion, parallel / serial conversion, and error correction is included in the second signal processing unit or the like.

  In the above description, although the right singular vector of singular value decomposition is used, the left singular vector obtained by singular value decomposition of the matrix obtained by transposing the matrix subjected to singular value decomposition is the singular value decomposition of the non-transposed matrix. It is equivalent to the right singular vector. Similarly, even if the original channel vector is multiplied by the Hermitian conjugate vector to perform eigenvalue decomposition, a vector equivalent to the right singular vector or the left singular vector can be obtained. In this sense, the use of a mathematically equivalent vector to the “right singular vector” also falls within the intended “right singular vector” of the related art of the present invention. Similarly, utilizing a mathematically equivalent vector to the left singular vector also falls within the intended “left singular vector” range of the related art of the present invention.

  Furthermore, in the above description, only the virtual transmission path corresponding to the first singular value is used between each first signal processing unit on the base station side and the terminal station apparatus, and the singular value after the second singular value is used. It has been described that the virtual transmission line corresponding to is not used, but, for example, in the case of using a shared antenna relating to a plurality of polarizations such as V polarization and H polarization, each first signal processing unit In order to utilize the virtual transmission line corresponding to the first singular value in the polarization antenna, formally one virtual signal transmission line corresponding to two singular values is utilized in one first signal processing unit. It is equivalent to In particular, when there is a slight leak between polarizations, the first signal processing unit collectively accommodates and performs signal processing on all two types of polarization antennas to suppress crosstalk components between polarizations. In other words, using virtual transmission paths corresponding to the first singular value and the second singular value is superior in transmission efficiency. In this case, the mathematical expression corresponds to utilizing the first singular value and the second singular value, but in the practical sense, virtual transmission paths corresponding to the first singular value are provided for each polarization antenna group. It corresponds to using. The intention of the present invention is that, in the case of utilizing a plurality of antenna groups which are expected to be very low in correlation with each other as in the case of utilizing such polarized antennas, signal processing or circuit Even in the case where the same first signal processing unit is used, the case where the virtual transmission paths corresponding to the first singular value effectively corresponding to the respective antenna groups are used in parallel, Spatial multiplexing transmission utilizing a virtual transmission path corresponding to a first singular value in an effective sense is to be transmitted using a plurality of first signal processing units. In addition, in the plurality of first signal processing units included in the base station apparatus, upconversion and downconversion processing between the baseband and the radio frequency are basically performed using individual local oscillator signals. However, it is preferable that the signals of the respective local oscillators behave as quasi-synchronously as possible, and for this purpose, a reference signal such as a common reference clock may be supplied from the third signal processing unit. Alternatively, a radio signal for performing up conversion and down conversion between the baseband and the radio frequency by supplying a reference signal of an intermediate frequency from the second signal processing unit to the first signal processing unit and performing, for example, multiplication processing thereof. It is also possible to generate a signal of frequency. Depending on the value of the intermediate frequency used here and the stability of the circuit that performs multiplication processing, the uncertainty of the complex phase of the wireless signal among the plurality of first signal processing units is limited also in the transmission signal processing. In this case, it also becomes possible to perform precoding processing among the plurality of first signal processing units in the second signal processing unit. However, basically, the reference signals supplied from at least the second signal processing unit to the plurality of first signal processing units are on the cable between the plurality of first signal processing units in the second signal processing unit. In order to reduce the loss of the signal, it is fundamental to set the frequency to 1/2 or less of the frequency of the local signal used for upconversion and downconversion processing between baseband and radio frequency, and in this sense the local oscillator It becomes independent between the signal processing units. However, when the base station apparatus and the terminal station apparatus are arranged in a short distance, L in equation (18) becomes smaller, and as a result, the distance between the first signal processing units can be shortened. Depending on the value of the cable loss, the second signal processing unit may directly supply the signal of the local oscillator to the plurality of first signal processing units.

  Also, in the above description, the multiplication processing of the transmission / reception signal and the transmission / reception weight has been described as being performed on the baseband, but it shows a typical signal processing, and a signal processing equivalent to that is a baseband signal It is of course also possible to implement on an intermediate frequency (IF) (Intermediate Frequency) signal between RF and RF signals. Although it is easier to perform processing in a lower frequency band in terms of signal processing, in the 5th generation mobile communication, since communication is performed in a bandwidth of several hundred to 1 GHz in a high frequency band such as a millimeter wave band, Even if the frequency is processed in the IF band of several GHz, the processing difficulty does not greatly change. The baseband signal or baseband in the present specification is used in a broad sense of a frequency band capable of performing digital signal processing, and in this sense, an IF band different from the baseband in a narrow sense. It is possible to apply the present invention essentially even to the signal processing in the case, and the claims of the present invention include such broad baseband signals and basebands.

  Further, according to the present invention, since the number of antenna elements included in the radio station apparatus is enormous, even if a few of the antenna elements among them are subjected to exceptional signal processing, the remaining majority of the antenna elements can be It is possible to obtain generally expected characteristics by the effect. However, even if such a part of antenna elements is processed exceptionally, the result of signal processing using the remaining antenna elements will determine most of the characteristics in most cases. Even if the application of the exception processing is performed, if the effect is limited without obtaining the expansion effect by the exception application, it should be the scope of the present invention.

  The base station apparatus and the terminal station apparatus in the related art described above may be realized by a computer. In that case, a program for realizing this function may be recorded in a computer readable recording medium, and the program recorded in the recording medium may be read and executed by a computer system. Here, the “computer system” includes an OS and hardware such as peripheral devices. The term "computer-readable recording medium" refers to a storage medium such as a flexible disk, a magneto-optical disk, a ROM, a portable medium such as a ROM or a CD-ROM, or a hard disk built in a computer system. Furthermore, the "computer-readable recording medium" dynamically holds a program for a short time, like a communication line when transmitting a program via a network such as the Internet or a communication line such as a telephone line. It may also include one that holds a program for a certain period of time, such as volatile memory in a computer system that becomes a server or a client in that case. Further, the program may be for realizing a part of the functions described above, and may be capable of realizing the functions described above in combination with a program already recorded in a computer system. It may be realized using hardware such as PLD (Programmable Logic Device) or FPGA (Field Programmable Gate Array).

  Although the embodiments of the present invention have been described above with reference to the drawings, it is apparent that the above embodiments are merely examples of the present invention, and the present invention is not limited to the above embodiments. is there. Therefore, additions, omissions, substitutions, and other modifications of the components may be made without departing from the technical spirit and scope of the present invention.

1 ... Base station apparatus,
2 ... Radio station apparatus,
3 ... prospect wave,
4 ... Stable reflection wave by structure,
5 ... Multiple reflections near the ground,
6 ... Multiple reflections near the ground,
7 ... structure, 11 ... transmitting station,
12 ... receiving station,
40 ... wireless communication system,
50: Wireless communication system,
53 ... wireless communication system,
60 ... terminal station apparatus,
61: Transmission unit,
65: Reception unit,
67 ... interface circuit,
68 MAC layer processing circuit
70: Base station apparatus,
71 ... second transmission signal processing unit,
75: second received signal processing unit,
77: Interface circuit,
78 MAC layer processing circuit
80: Base station apparatus,
81: Transmission unit,
85: Reception unit,
87: interface circuit,
88 MAC layer processing circuit
111 ... first transmission signal processing circuit,
120 ... communication control circuit,
121 ... communication control circuit,
130 ... first transmission weight processing unit,
131: First channel information acquisition circuit,
132: first channel information storage circuit,
133: first transmission weight calculation circuit,
140: first transmission weight processing unit,
141: Channel information acquisition circuit,
142: Channel information storage circuit,
143: first transmission weight calculation circuit,
144: first reception weight processing unit,
145: Reception signal processing circuit,
146: first channel information estimation circuit,
147: first reception weight calculation circuit,
148: second transmission signal processing circuit,
149: Transmission weight calculation circuit,
154: first reception weight processing unit,
155: first received signal processing circuit,
156: first channel information estimation circuit,
157: first reception weight calculation circuit,
158: first reception signal processing circuit,
159 ... second received signal processing circuit,
160: first reception weight processing unit,
161: first channel information estimation circuit,
162: first reception weight calculation circuit,
181 ... first transmission signal processing unit,
185: first received signal processing unit,
190 ... second reception signal processing circuit,
191: Channel matrix acquisition circuit,
192 ... reception weight matrix calculation circuit,
193 ... reception weight matrix multiplication circuit,
194: Signal detection circuit,
301: Base station apparatus,
302: Terminal station apparatus,
303 ... base station apparatus,
304: first signal processing unit,
305: second signal processing unit,
306 ... base station apparatus,
307 ... dish antenna,
310 ... base station apparatus antenna,
312 ... terminal station apparatus antenna element group,
320 ... terminal station apparatus antenna element group,
501: terminal station apparatus,
502 ... antenna element,
511: first signal processing unit,
513 ... direction in which the antenna elements of the terminal station apparatus are arranged,
514: Direction in which the first signal processing units are arranged,
515 ... service area,
533: Direction in which the linear array antennas are arranged,
600A, 600B, 600C, 600D ... terminal station apparatus,
601 ... housing,
602 ... display,
603 ... housing,
605 ... guiding part,
607 ... housing,
609 ... housing,
610 ... two-dimensional array antenna,
611 ... antenna substrate,
612 ... antenna element,
613 ... hinge part,
620 ... two-dimensional array antenna,
621 ... antenna substrate,
622 ... antenna element,
623 ... groove,
630 ... two-dimensional array antenna,
631 ... antenna substrate,
632 ... antenna element,
633 ... hinge part,
640 ... linear array antenna,
641 ... antenna substrate,
642 ... antenna element,
643 ... hinge part,
781 ... scheduling processing circuit,
811 ... Transmission signal processing circuit,
812 ... addition synthesis circuit,
813 ... IFFT & GI addition circuit,
814 ... D / A converter,
815 ... Local oscillator,
816 ... mixer,
817 ... filter,
818 ... High Power Amplifier,
819 ... antenna element,
820 ... communication control circuit,
821 ... first transmission signal processing circuit,
830 ... Transmission weight processing unit,
831 ... channel information acquisition circuit,
832: Channel information storage circuit,
833 ... multi-user MIMO transmission weight calculation circuit,
851 ... antenna element,
852 ... Low noise amplifier (LNA),
853 ... Local Oscillator,
854 ... mixer,
855 ... filter,
856 ... A / D converter,
857 ... FFT circuit,
858 ... received signal processing circuit,
860: Reception weight processing unit
861 ... channel information estimation circuit,
862 ... multi-user MIMO reception weight calculation circuit,
881 ... scheduling processing circuit

Claims (8)

A terminal station apparatus in a wireless communication system comprising: a base station apparatus comprising a plurality of first antenna elements; and at least one terminal station apparatus,
And
An antenna substrate movably attached to the housing;
A plurality of second antenna elements disposed on the main surface of the antenna substrate;
Equipped with
When at least a part of the plurality of second antenna elements is accommodated in the housing, a wireless signal is not transmitted from the plurality of second antenna elements, and all of the plurality of second antenna elements are A wireless signal is transmitted from the plurality of second antenna elements when not accommodated in the housing.
Terminal station device. The antenna substrate is a rectangular plate having a predetermined thickness,
One side of the antenna substrate is attached to the housing via a hinge portion,
The antenna substrate rotates about the hinge portion.
The terminal station apparatus according to claim 1. The antenna substrate is a rectangular plate having a predetermined thickness,
The antenna substrate is attached via a guide provided on the housing,
The guiding unit guides the moving direction of the antenna substrate to be parallel to the main surface of the housing.
The terminal station apparatus according to claim 1. A terminal station apparatus in a wireless communication system comprising: a base station apparatus comprising a plurality of first antenna elements; and at least one terminal station apparatus,
And
An antenna substrate movably attached to the housing;
A plurality of second antenna elements disposed on the main surface of the antenna substrate;
Equipped with
The antenna substrate is a fan-shaped plate having a constant thickness,
The antenna substrate is attached to the housing via a hinge portion attached to a main portion near the fan-shaped,
By the antenna substrate is rotated by the hinge portion to the axis, the whole of the antenna substrate is accommodated in the housing,
Terminal station device. The antenna substrate is an elongated rectangular plate having a constant thickness,
One end of the antenna substrate is attached to the housing via a hinge portion,
The antenna substrate rotates about the hinge portion.
The terminal station apparatus according to claim 1. The signal processing unit further includes a signal processing unit that performs signal processing of wireless communication with the base station apparatus,
The signal processing unit
At least one of a transmission weight vector and a reception weight vector for a MIMO channel matrix used for wireless communication between the first antenna element and the second antenna element corresponds to a first singular value of the MIMO channel matrix. 1) A transmission weight vector calculated or calculated based on at least one of at least one of the right singular vector and the first left singular vector or an approximate solution of the first right singular vector and an approximate solution of the first left singular vector or Transmit one or more independent signal sequences using the receive weight vector,
The terminal station apparatus as described in any one of Claims 1-5. There line wireless communications with a base station apparatus comprising a plurality of first antenna elements, an antenna substrate movably mounted second antenna element of the plurality to the main surface is relative to the housing and housing A control method of a terminal station device having an arranged antenna substrate , comprising:
The signal processing unit does not transmit a radio signal from the plurality of second antenna elements when at least a part of the plurality of second antenna elements is accommodated in the housing, and the plurality of second Transmitting a wireless signal from the plurality of second antenna elements when all of the antenna elements are not accommodated in the housing;
A control method of a terminal station apparatus having: A method of manufacturing a terminal station apparatus that performs wireless communication with a base station apparatus including a plurality of first antenna elements, comprising:
A first step of movably attaching a fan-shaped antenna substrate having a certain thickness to a housing of the terminal station apparatus via a hinge attached near the main part of the fan-shaped;
A second step of arranging a plurality of second antenna elements on the main surface of the antenna substrate;
Have
By rotating the antenna substrate about the hinge portion, the entire antenna substrate is housed in the housing.
A method of manufacturing a terminal station device.

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