JP4707631B2 - Polar modulation transmission apparatus and radio communication apparatus - Google Patents

Description

  The present invention relates to a polar modulation transmission apparatus and a radio communication apparatus. More specifically, even in a modulation scheme having a wide dynamic range of transmission power, the modulation accuracy and distortion characteristics are maintained well up to a low output, and power efficiency is improved. The present invention relates to a good polar modulation transmission apparatus and a wireless communication apparatus using the same.

  Conventionally, a high-frequency power amplifier that amplifies a modulation signal including an envelope fluctuation component uses a class A or AB class linear amplifier to linearly amplify the envelope fluctuation component. Such a linear amplifier is excellent in linearity, but consumes electric power associated with a DC bias component at all times, and therefore has lower power efficiency than a non-linear amplifier of class C or class E. For this reason, when such a high frequency power amplifier is applied to a portable wireless communication apparatus using a battery as a power source, there is a problem that the usage time is shortened because the power consumption of the high frequency power amplifier is large. . In addition, when such a high-frequency power amplifier is applied to a base station apparatus of a wireless system in which a plurality of high-power transmission apparatuses are installed, there is a problem that the apparatus becomes large and the amount of heat generation increases. .

  In order to solve such a problem, a transmitter using a polar modulation scheme has been proposed as a transmitter that operates with high power efficiency. In the polar modulation method, a baseband signal is separated into an amplitude signal and a phase signal, and then amplitude modulation and phase modulation are performed independently (see, for example, FIG. 10). In the example of FIG. 10, the high frequency phase modulation signal phase-modulated based on the phase signal and the amplitude signal are multiplied by a multiplier to generate a high frequency transmission signal. The transmission apparatus using the polar modulation method can improve the power efficiency because the high-frequency power amplifier serving as a multiplier can perform a non-linear operation (saturation operation). Techniques using this type of polar modulation method are described in, for example, Patent Document 1 and Patent Document 2.

  FIG. 11 is a diagram illustrating an example of functional blocks of a conventional transmission device 500 using a polar modulation scheme. In FIG. 11, a conventional transmission apparatus 500 includes an amplitude phase separation unit 501, a multiplier 502, an amplitude signal amplifier 503, a phase modulation unit 504, a variable gain amplifier 505, a high frequency power amplifier 506, a digital-analog converter (hereinafter referred to as D). / A converter) 507, and a digital-analog converter (hereinafter referred to as D / A converter) 508.

  The amplitude phase separation unit 501 separates the input modulation baseband signal S51 into an amplitude signal S52 and a phase signal S53. The multiplier 502 receives an amplitude signal S52 and a transmission power control signal S54 for controlling the magnitude of transmission power. Multiplier 502 multiplies amplitude signal S52 and transmission power control signal S54, and outputs the result as amplitude signal S55 subjected to transmission power control. The amplitude signal S55 is converted into an analog signal S56 by the D / A converter 507, and is supplied as a power supply voltage S57 to the high-frequency power amplifier 506 that performs nonlinear operation (saturation operation) via the amplitude signal amplifier 503.

  On the other hand, the phase signal S53 is input to the phase modulation unit 504. The phase modulation unit 504 phase-modulates the carrier wave signal with the phase signal S53, and outputs the phase-modulated signal as the high-frequency phase modulation signal S58. The high frequency phase modulation signal S58 is input to the variable gain amplifier 505. The gain of the variable gain amplifier 505 is controlled by an analog signal S62 obtained by D / A converting a gain control digital signal S61 from a control unit (not shown). The variable gain amplifier 505 amplifies the high frequency phase modulation signal S58 and outputs it as a high frequency phase modulation signal S59. The high frequency phase modulation signal S59 is input to the high frequency power amplifier 506. The high frequency power amplifier 506 performs amplitude modulation on the high frequency phase modulation signal S59 based on the power supply voltage S57 supplied from the amplitude signal amplifier 503, and outputs the result as a high frequency transmission signal S60.

  Next, the operation of the conventional transmission apparatus 500 will be described in detail using mathematical expressions. First, assuming that the modulation baseband signal S1 is Si (t), Si (t) can be expressed by Expression (1) using a complex number display.

Si (t) = a (t) · exp [jφ (t)] (1)
Here, a (t) represents amplitude data, and exp [jφ (t)] represents phase data. The amplitude phase separation unit 501 extracts amplitude data a (t) and phase data exp [jφ (t)] from the modulation baseband signal Si (t). Here, the amplitude data a (t) corresponds to the amplitude signal S52, and the phase data exp [jφ (t)] corresponds to the phase signal S53. The amplitude data a (t) is multiplied by the power information G indicated by the transmission power control signal S54 by the multiplier 502, and output as amplitude data G · a (t) subjected to transmission power control. The amplitude data G · a (t) is amplified by the amplitude signal amplifier 503 and supplied to the high frequency power amplifier 506 as a power supply voltage.

  The phase modulation unit 504 modulates the carrier wave having the angular frequency ωc with the phase data exp [jφ (t)] to generate the high-frequency phase modulation signal S58. Here, when the high-frequency phase modulation signal S58 is Sc, Sc can be expressed by Expression (2).

Sc = exp [j (ωc × t + φ (t))] (2)
The high-frequency power amplifier 506 multiplies the above-described amplitude data G · a (t) by the high-frequency phase modulation signal S59 input via the variable gain amplifier 505, and outputs the result as a high-frequency transmission signal S60. When the high-frequency transmission signal S60 is an RF signal Srf, the RF signal Srt can be expressed by Expression (3).

Srf = G · a (t) · exp [j (ωc × t + φ (t))] (3)
Since the conventional transmission apparatus 500 using the polar modulation method controls the amplitude (envelope) of the signal output from the high-frequency power amplifier 506 with the power supply voltage, the high-frequency power amplifier 506 can be operated in a saturated manner. Can be high.
Japanese Patent No. 3207153 JP 2001-156554 A

  However, the conventional polar modulation transmission apparatus 500 has the following problems.

  The dynamic range of transmission power differs depending on the wireless communication system, but when the dynamic range on the low output side becomes wider, that is, in the wireless communication system with a small minimum transmission power, a small signal is required as an amplitude signal. Is done. Therefore, in the conventional polar modulation transmission apparatus 500, a minute signal is required for the amplitude signal 55 after transmission power control.

  FIG. 12 is a diagram illustrating a difference in the change range of the amplitude signal S55 depending on the transmission power. In FIG. 12, the horizontal axis indicates the amplitude signal S55 in a true number in volts (V), and the change range of the amplitude signal S55 depending on the magnitude of the transmission power is represented by an arrow as a continuous signal. The scale on the horizontal axis schematically shows that the value is discretized (quantized) when the amplitude signal S55 is expressed as a digital signal. As described above, when the amplitude signal S55 expressed as a true number is handled as a digital signal, the ratio of the quantization noise to the change range of the amplitude signal S55 increases when the transmission power is small. That is, when the transmission power is small, the representation accuracy of the amplitude signal S55 is deteriorated due to the quantization noise, and this causes an ACLR (Adjacent Channel Leakage power Ratio) representing distortion of the transmission signal and an EVM (Error Vector Magnitude) representing modulation accuracy. It will deteriorate.

  The simulation results of the influence of quantization noise on ACLR and EVM when the amplitude signal S55 expressed as a true number is handled as a digital signal are shown in FIGS. 13 and 14, respectively. FIG. 13 is a diagram illustrating a result of simulating the influence of quantization noise on ACLR. FIG. 14 is a diagram illustrating a result of simulating the influence of quantization noise on the EVM. In the simulation, an EDGE (Enhanced Data GSM Environment) modulation signal was used.

  In FIG. 13, ACLR indicates the result of 400 kHz detuning (see FIG. 13A) and the result of 600 kHz detuning (see FIG. 13B). In FIG. 14, EVM represents RMS EVM in the standard of 3GPP (3rd Generation Partnership Project). The simulation was performed with four types of quantization bits of 14 bits, 12 bits, 10 bits, and 8 bits. Further, in order to see the influence of quantization noise, the characteristic of the high-frequency power amplifier 506 at the final stage where polar modulation is performed is assumed to be an ideal linear characteristic (no distortion).

  As shown in FIGS. 13 and 14, when the amplitude signal S55 expressed as a true number is handled as a digital signal, it is understood that the ACLR and EVM deteriorate as the transmission power decreases. Further, when comparing with the same transmission power, it can be seen that the smaller the number of bits of quantization, the greater the degradation of ACLR and EVM.

  In the above description, degradation of ACLR and EVM caused by quantization noise when the amplitude signal S55 is handled as a digital signal has been described. However, when the amplitude signal S55 is handled as an analog signal, the amplitude signal S55 is very small. Since the SN ratio (signal-to-noise ratio) is degraded, the ACLR and EVM are degraded qualitatively as described above.

  Therefore, an object of the present invention is to solve the above-mentioned problems. Even in a modulation scheme with a wide dynamic range of transmission power, a polar system that maintains good modulation accuracy and distortion characteristics up to low output and has good power efficiency. A modulation transmission apparatus is provided.

  The present invention is directed to a polar modulation transmission apparatus. In order to achieve the above object, the polar modulation transmission apparatus of the present invention includes an amplitude phase separation unit that separates a modulation baseband signal into an amplitude signal and a phase signal, and performs a true / logarithmic conversion of the amplitude signal, A first logarithm / logarithm conversion unit that outputs as a logarithmically expressed amplitude signal, and a second logarithm / logarithm that outputs the logarithmically expressed transmit power control signal by performing logarithm / logarithm conversion on the transmission power control signal A conversion unit, an adder that adds a logarithmically expressed transmission power control signal to a logarithmically expressed amplitude signal, and outputs the resultant signal as a transmission power controlled amplitude signal; A logarithm / integer conversion unit that converts and outputs as an amplitude signal expressed as a true number; a phase modulation unit that performs phase modulation on the high frequency carrier signal based on the phase signal and outputs the phase modulation signal; Power supply A high-frequency power amplifier that performs amplitude modulation on a high-frequency phase-modulated signal based on the pressure and outputs it as a high-frequency transmission signal, amplifies the amplitude signal expressed as a true number, and uses the amplified amplitude signal as a power supply voltage And an amplitude signal amplifier to be supplied.

  As a result, the polar modulation transmission apparatus suppresses deterioration of the representation accuracy of the amplitude signal due to deterioration of quantization noise and SN ratio (signal-to-noise ratio) even when the transmission power is small and the amplitude signal is small, and deterioration of ACLR and EVM is suppressed. Can be suppressed. Moreover, since it is not necessary to provide a multiplier for multiplying the amplitude signal and the transmission power control signal, the circuit scale can be greatly reduced.

  Preferably, the high frequency power amplifier operates as a non-linear amplifier, and performs amplitude modulation on the high frequency phase modulation signal according to the transmission power control signal and the amplitude signal.

  Preferably, the polar modulation transmission apparatus further includes a variable gain amplifier that amplifies the high-frequency phase modulation signal with a controlled gain, following the phase modulation unit.

  Preferably, the amplitude signal amplifier includes a switching regulator or a class D amplifier. As a result, the power efficiency of the amplitude signal amplifier can be improved. In addition, the power efficiency of the entire transmission device can be improved.

The polar modulation transmission apparatus may further include a second adder for adjusting transmission power between the adder and the logarithm / integer conversion unit. The second adder adds a gain adjustment value to the power-controlled amplitude signal. As a result, individual variations in output power can be easily adjusted at the time of manufacture, and the gain of the amplitude signal can be adjusted.
The

  The amplitude signal amplifier selectively supplies either a power supply voltage corresponding to the amplitude signal and the transmission power control signal or a predetermined fixed value power supply voltage to the high frequency power amplifier according to the magnitude of the transmission power. May be. When the power supply voltage corresponding to the amplitude signal and the transmission power control signal is selected, the high frequency power amplifier operates as a non-linear amplifier, and the transmission power control signal is applied to the high frequency phase modulation signal amplified by the variable gain amplifier. Then, amplitude modulation according to the amplitude signal is performed and output as a high-frequency transmission signal. On the other hand, when a predetermined fixed value power supply voltage is selected, the variable gain amplifier performs amplitude modulation according to the transmission power control signal and the amplitude signal on the high-frequency phase modulation signal output from the phase modulation unit. The high-frequency power amplifier operates as a linear amplifier, amplifies the signal subjected to amplitude modulation by the variable gain amplifier with a constant gain according to a predetermined fixed value power supply voltage, and outputs the amplified signal as a high-frequency transmission signal.

  Accordingly, the polar modulation transmission apparatus can select whether to perform amplitude modulation with the high-frequency power amplifier or to perform amplitude modulation with the variable gain amplifier according to the magnitude of the transmission power. For this reason, the polar modulation transmission apparatus can maintain good distortion characteristics and modulation accuracy of the transmission signal regardless of the transmission power range.

  Preferably, the polar modulation transmission apparatus further includes a third adder for adjusting transmission power between the adder and the variable gain amplifier. The third adder adds a gain adjustment value to the transmission power-controlled amplitude signal. As a result, the gain difference with respect to the amplitude signal due to the difference between the high-frequency power amplifier and the variable gain amplifier can be adjusted. Also, individual variations of the variable gain amplifier can be adjusted at the time of manufacture.

  Preferably, the polar modulation transmission apparatus further includes a D / A converter at any position up to the previous stage of the logarithm / integer conversion unit. An analog signal that has passed through the D / A converter is input to the logarithm / integer conversion unit. As a result, the logarithm / logarithm conversion unit can realize logarithm / logarithm conversion relatively easily by utilizing the exponential characteristic of the analog input / output of the bipolar transistor. In addition, it is possible to suppress the influence of quantization noise that becomes noticeable with a small signal in a digital circuit, and to make the effect of logarithmically expressing an amplitude signal more remarkable.

  The polar modulation transmitter is connected to any position up to the preceding stage of the high-frequency power amplifier, and the amplitude supplied in advance as a power supply voltage to the high-frequency power amplifier so that at least distortion generated in the high-frequency power amplifier is suppressed. You may further provide the distortion compensation part which distorts a signal. Thereby, the polar modulation transmission apparatus can realize an operation with lower distortion.

  The present invention is also directed to a wireless communication device. The wireless communication device includes a transmission circuit that generates a transmission signal and an antenna that outputs the transmission signal generated by the transmission circuit. The polar modulation transmission apparatus described above is used for the transmission circuit. In addition, the wireless communication device includes a reception circuit that processes a reception signal received from the antenna, an antenna sharing unit that outputs the transmission signal generated by the transmission circuit to the antenna, and outputs the reception signal received from the antenna to the reception circuit; May be further provided.

  As a result, the wireless communication device can widen the control range of the transmission power of the transmission circuit, and can maintain the modulation accuracy and distortion characteristics well up to a low output, thereby realizing excellent ACLR and EVM characteristics over a wide transmission power. can do. In addition, since the power efficiency of the transmission circuit is high, it is possible to extend the usage time of the mounted battery power supply.

  As described above, in the polar modulation transmission apparatus of the present invention, the logarithm / logarithm conversion unit performs logarithm / logarithm conversion on the amplitude signal and the transmission power control signal, and the logarithmically expressed amplitude signal and logarithmically expressed transmission. Output as a power control signal. Thus, the polar modulation transmission apparatus can realize transmission power control for the amplitude signal only by adding the logarithmically expressed amplitude signal and the logarithmically expressed transmission power control signal. Further, since the transmission apparatus does not need to include a multiplier for multiplying the amplitude signal and the transmission power control signal, the circuit scale can be greatly reduced.

  Further, since the polar modulation transmission apparatus handles logarithmically expressed amplitude signals, the ratio of quantization noise to the amplitude signal change range becomes equal regardless of the magnitude of transmission power. For this reason, the polar modulation transmission apparatus suppresses the deterioration of the representation accuracy of the amplitude signal due to the deterioration of the quantization noise and the SN ratio (signal-to-noise ratio) even when the transmission power is small and the amplitude signal is small, and ACLR and EVM are suppressed. Can be prevented. As a result, the polar modulation transmission apparatus can maintain good modulation accuracy and distortion characteristics up to a low output and achieve high power efficiency even in a modulation system with a wide dynamic range of transmission power.

  These and other objects, features, aspects and advantages of the present invention will become more apparent from the following detailed description when taken in conjunction with the accompanying drawings.

  Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.

(First embodiment)
FIG. 1 is a block diagram showing an example of a schematic configuration of a polar modulation transmission apparatus 100 according to the first embodiment of the present invention. In FIG. 1, a polar modulation transmission apparatus (hereinafter simply referred to as a transmission apparatus) 100 includes an amplitude phase separation unit 101, an adder 102, an amplitude signal amplifier 103, a phase modulation unit 104, a variable gain amplifier 105, a high frequency power amplifier 106, A D / A converter 107, a D / A converter 108, a true number / logarithm conversion unit 109, a true number / logarithm conversion unit 110, and a logarithm / logarithm conversion unit 111 are provided.

  The transmission apparatus 100 modulates the modulation baseband signal S1 using a polar modulation method, and outputs the modulated baseband signal S1 as a high-frequency transmission signal S10. Details of the operation of the transmission apparatus 100 will be described below. The modulation baseband signal S1 is input to the amplitude / phase separation unit 101 as a digital signal. The amplitude phase separation unit 101 separates the input modulation baseband signal S1 into an amplitude signal S2 and a phase signal S3.

  The amplitude signal S2 is input to the true / logarithm conversion unit 110. The logarithm / logarithm conversion unit 110 performs logarithm / logarithm conversion on the input amplitude signal S2 and outputs the logarithmically expressed amplitude signal S14. The true / logarithm conversion unit 109 receives a transmission power control signal S4 for controlling the magnitude of transmission power. The true number / logarithm conversion unit 109 performs a true number / logarithm conversion on the transmission power control signal S4 and outputs it as a logarithmically expressed transmission power control signal S13. The true number / logarithm conversion units 109 and 110 may realize the true number / logarithmic conversion by a digital circuit that performs a logical operation, or use a ROM table or the like that defines an input / output (true number / logarithm) relationship. A true / logarithmic conversion may be realized.

  The transmission power control signal S13 and the amplitude signal S14 are input to the adder 102. The adder 102 adds the transmission power control signal S13 to the amplitude signal S14, and outputs the result as an amplitude signal S5 subjected to transmission power control. The amplitude signal S5 is converted into an analog signal S16 by the D / A converter 107. The transmission device 100 may include a low-pass filter (not shown) after the D / A converter 107.

  The analog signal S16 is logarithm / logarithmically converted by the logarithm / logarithm conversion unit 111 and output as an amplitude signal S6 expressed as a logarithm. The amplitude signal S6 is amplified in current drive capability by the amplitude signal amplifier 103 and supplied to the high frequency power amplifier 106 as the power supply voltage S7. Here, the amplitude signal amplifier 103 is preferably composed of a switching regulator or a class D amplifier in order to increase power efficiency.

  On the other hand, the phase signal S 3 is input to the phase modulation unit 104. The phase modulation unit 104 performs phase modulation on the carrier wave signal based on the phase signal S3 and outputs the result as a high-frequency phase modulation signal S8. The high-frequency phase modulation signal S8 is input to the variable gain amplifier 105. The gain of the variable gain amplifier 105 is controlled by an analog signal S12 obtained by D / A converting the digital signal S11 from a control unit (not shown). The variable gain amplifier 105 amplifies the high frequency phase modulation signal S8 and outputs it as a high frequency phase modulation signal S9.

  The high frequency phase modulation signal S9 is input to the high frequency power amplifier 106. The high frequency power amplifier 106 performs amplitude modulation on the high frequency modulation signal S9 based on the amplitude signal S7 supplied as the power supply voltage from the amplitude signal amplifier 103, and outputs the result as a high frequency transmission signal S10.

  Since the transmission apparatus 100 handles the logarithmically expressed amplitude signal S14 and the logarithmically expressed transmission power control signal S13, the adder 102 can perform an operation associated with transmission power control that originally requires a multiplier. For this reason, the transmission apparatus 100 does not need to include a multiplier, and the circuit scale can be greatly reduced.

  Further, since the amplitude signal S5 subjected to transmission power control is expressed logarithmically, even if it is expressed as a true number, even a minute value can be expressed in the same change range as when it is a large value. it can. FIG. 2 is a diagram illustrating the difference in the change range of the amplitude signal S5 depending on the magnitude of the transmission power. In FIG. 2, the horizontal axis represents the amplitude signal S5 in a logarithm in dBV units, and the change range of the amplitude signal S5 depending on the magnitude of the transmission power is represented by an arrow as a continuous signal. The scale on the horizontal axis schematically shows that the value is discretized (quantized) when the amplitude signal S5 is expressed as a digital signal.

  As shown in FIG. 2, when the logarithmically expressed amplitude signal S5 is handled as a digital signal, the change range of the amplitude signal S5 is equal regardless of the magnitude of the transmission power, and the quantization with respect to the change range of the amplitude signal S5 is performed. It can be seen that the noise ratio is also equal. That is, even when the transmission power is small, the representation accuracy of the amplitude signal S5 is not deteriorated due to the quantization noise, and the degradation of the ACLR indicating the distortion of the transmission signal and the EVM indicating the modulation accuracy can be prevented.

  The results of simulating the influence of quantization noise on ACLR and EVM when the logarithmically expressed amplitude signal S5 is handled as a digital signal are shown in FIGS. 3 and 4, respectively. FIG. 3 is a diagram illustrating a result of simulating the influence of quantization noise on ACLR. FIG. 4 is a diagram illustrating a result of simulating the influence of quantization noise on the EVM. In the simulation, an EDGE modulation signal was used.

  In FIG. 3, ACLR shows the result of 400 kHz detuning (see FIG. 3 (a)) and 600kHz detuning (see FIG. 3 (b)), and EVM is the result of 3GPP (3rd Generation Partnership Project). Represents RMS EVM in the standard. The simulation was performed with four types of quantization bits of 14 bits, 12 bits, 10 bits, and 8 bits. In order to see the influence of the quantization noise, it is assumed that the characteristic of the high-frequency power amplifier 106 at the final stage where polar modulation is performed is an ideal linear characteristic (no distortion).

  As shown in FIGS. 3 and 4, when the logarithmically expressed amplitude signal S5 is handled as a digital signal, it can be seen that even when the transmission power is reduced, the ACLR and EVM are not deteriorated. In ACLR at 600 kHz detuning, the amount of distortion decreases as the number of bits for quantization increases. This is because the minimum value of the amount of distortion is limited by quantization noise.

  In the above description, degradation of ACLR and EVM caused by quantization noise when the amplitude signal S5 is handled as a digital signal has been described. However, when the amplitude signal S5 is handled as an analog signal, the amplitude signal S5 is very small. Since the SN ratio (signal-to-noise ratio) is degraded, the ACLR and EVM are degraded qualitatively as described above. Therefore, the effect of the present invention can be obtained similarly when the amplitude signal S5 is handled as an analog signal. The transmitter 100 does not need to include the D / A converter 107 when the amplitude signal S5 is handled as an analog signal.

  In the present invention, the functional blocks up to the previous stage of the logarithm / true number conversion unit 111 (amplitude phase separation unit 101, true number / logarithm conversion units 109 and 110, addition unit 102, and the like) are configured by digital circuits. However, these functional blocks may be configured by analog circuits. Therefore, the D / A converter 107 may be connected not only to the position shown in FIG. 1 but also to an arbitrary position.

  However, it is desirable that an analog signal is input to the logarithm / integer conversion unit 111. The reason will be described below. The logarithm / logarithm conversion unit 111 can realize logarithm / logarithm conversion relatively easily by using the exponential characteristic of the analog input / output of the bipolar transistor. Therefore, it is desirable that the logarithm / true number conversion unit 111 is configured by an analog circuit, and an analog signal after D / A conversion is input.

  Further, although the transmission apparatus 100 performs the true / logarithmic conversion of the transmission power control signal S4 and the amplitude signal S2 by the true / logarithm conversion units 109 and 110, the amplitude / phase separation unit 101 and the control unit (not shown) If the amplitude signal and the transmission power control signal expressed logarithmically are directly input to the adder 102, it is not necessary to provide the true / logarithm conversion units 109 and 110, and the circuit scale can be reduced. Further, the transmission apparatus 100 does not necessarily include the variable gain amplifier 105 and the D / A converter 108 when the magnitude of the high-frequency phase modulation signal S8 is appropriate.

  As described above, in the transmission device 100 according to the first embodiment of the present invention, the true number / logarithm conversion units 110 and 109 perform the true number / logarithm conversion on the amplitude signal S2 and the transmission power control signal S4, and logarithmically. The amplitude signal S14 expressed and the transmission power control signal S13 expressed logarithmically are output. As a result, the transmission apparatus 100 can realize transmission power control for the amplitude signal only by adding the logarithmically expressed amplitude signal S14 and the logarithmically expressed transmission power control signal S13. In addition, since the transmission apparatus 100 does not need to include a multiplier for multiplying the amplitude signal and the transmission power control signal, the circuit scale can be significantly reduced.

  Further, since the transmission apparatus 100 handles the logarithmically expressed amplitude signal, the ratio of the quantization noise to the amplitude signal change range becomes equal regardless of the magnitude of the transmission power. For this reason, the transmission apparatus 100 suppresses deterioration in the representation accuracy of the amplitude signal due to deterioration of quantization noise and SN ratio (signal-to-noise ratio) even when the transmission power is small and the amplitude signal is small. Deterioration can be prevented.

(Second Embodiment)
FIG. 5 is a block diagram showing an example of a schematic configuration of a polar modulation transmission apparatus 200 according to the second embodiment of the present invention. In FIG. 5, a polar modulation transmission apparatus (hereinafter simply referred to as a transmission apparatus) 200 includes an adder 114, an adder 115, a switch 112, and a switch 113, as compared with the transmission apparatus 100 according to the first embodiment. Further prepare.

  The transmission device 200 modulates the modulation baseband signal S1 using a polar modulation method, and transmits the modulated baseband signal S1 as a high-frequency transmission signal S10. Details of the operation of the transmission apparatus 200 will be described below. However, the same blocks and signals as those in the first embodiment are denoted by the same reference numerals and description thereof is omitted.

  Unlike the transmission apparatus 100 according to the first embodiment, the transmission apparatus 200 performs amplitude modulation with the high-frequency power amplifier 106 when the transmission power is large, and performs amplitude modulation with the variable gain amplifier 105 when the transmission power is small. Do.

  When the transmission power is large, it is desirable to operate the high-frequency power amplifier 106 as a nonlinear amplifier (in a nonlinear mode) from the viewpoint of power efficiency. On the other hand, when the transmission power is small and the high frequency power amplifier 106 is out of the range in which the high frequency power amplifier 106 can operate as a nonlinear amplifier, it is desirable to operate the high frequency power amplifier 106 as a linear amplifier (in a linear mode).

  Which mode the high-frequency power amplifier 106 is operated in is determined by a control unit (not shown) according to, for example, a transmission power control signal from the radio base station or transmission power based on the state of the received signal. .

  In FIG. 5, switches 112 and 113 switch the connection between the terminals ac and bc by a switching signal S21 output from the control unit according to the magnitude of transmission power. The transmission apparatus 200 switches the connection between the switches 112 and 113 based on the magnitude of the transmission power, so that the amplitude modulation is performed by the high frequency power amplifier 106 when the transmission power is large, and the variable gain amplifier 105 when the transmission power is small. Perform amplitude modulation with. Adders 114 and 115 add predetermined values given by signals S17 and S18 from the control unit to amplitude signal S5 output from adder 102, respectively.

  Here, the role of the adders 114 and 115 will be described in detail. Since the gain for the amplitude signal S5 is generally different between the case where the amplitude modulation is performed by the high frequency power amplifier 106 and the case where the amplitude modulation is performed by the variable gain amplifier 105, the adders 114 and 115 may change the amplitude as necessary. A predetermined value (a constant value) is added to the signal S5 to adjust the gain with respect to the amplitude signal S5. The adders 114 and 115 can also be used for the purpose of adjusting the output power variations caused by the individual variations of the high-frequency power amplifier 106 and the variable gain amplifier 105.

  First, when the transmission power is large and amplitude modulation is performed by the high-frequency power amplifier 106, the switch 112 and the switch 113 connect the terminal b and the terminal c, respectively. The gain of the variable gain amplifier 105 is controlled by an analog signal S12 obtained by D / A converting the digital signal S19 from a control unit (not shown). The variable gain amplifier 105 amplifies the high frequency phase modulation signal S8 and outputs it as a high frequency phase modulation signal S9. The high frequency power amplifier 106 performs amplitude modulation on the high frequency modulation signal S9 with the amplitude signal S7 supplied as the power supply voltage from the amplitude signal amplifier 103, and outputs the result as a high frequency transmission signal S10.

  Next, when the transmission power is small and amplitude modulation is performed by the variable gain amplifier 105, the switch 112 and the switch 113 connect the terminal a and the terminal c, respectively. As a result, the variable gain amplifier 105 receives an analog signal S12 obtained by D / A converting the amplitude signal S5 via the switch 113. The variable gain amplifier 105 performs amplitude modulation on the high-frequency phase modulation signal S8 according to the input analog signal S12. That is, the variable gain amplifier 105 performs amplitude modulation on the high frequency phase modulation signal S8 according to the transmission power control signal S4 and the amplitude signal S2.

  A signal indicating a predetermined fixed voltage value is input to the amplitude signal amplifier 103 as a fixed voltage value signal S20 from a control unit (not shown) via the switch 112. The fixed voltage value signal S20 is amplified by the amplitude signal amplifier 103 and supplied to the high frequency power amplifier 106 as a power supply voltage. For this reason, the high frequency power amplifier 106 operates as a linear amplifier, amplifies the high frequency phase modulation signal S9 amplitude-modulated by the variable gain amplifier 105 with a constant gain, and outputs it as a high frequency transmission signal S10.

Here, characteristics of a general variable gain amplifier will be described. In a general variable gain amplifier, the voltage gain V _out / V _in between the input and output is an exponential function of the gain control signal. An example of a circuit diagram of such a variable gain amplifier is shown in FIG.

In FIG. 6, V _in is a differential input signal, V _out is a differential output signal, V _d is a (differential) gain control signal, and V _cc is a power supply voltage. R _E is an emitter resistance, and R _L is a load resistance. Transistors Tr5, Tr6 of the differential input signal V _in is connected to the input terminal being input is grounded emitter flows differential current G _m · V _in the collector. Here, G _m can be expressed by Equation (4).

However, at room temperature, V _T has a value of about 26 mV.

Furthermore, the differential current is divided according to V _d by the transistors Tr1, Tr2, Tr3, Tr4 connected to the input terminal to which the gain control signal V _d is input, and a voltage drop occurs in the load resistance R _L. As a result, the relationship between the input and output voltage gains V _out / V _in can be expressed as in equation (5).

Expression (5) can be approximated as Expression (6) when V _d / V _T << − 1 (that is, when the input is sufficiently small).

In other words, the input-output voltage gain V _out / V _in is an exponential function of the gain control signal V _d .

  The variable gain amplifier 105 shown in FIG. 5 also has this exponential function characteristic. Therefore, the variable gain amplifier 105 includes a logarithm / integer conversion function. For this reason, the transmission apparatus 200 (see FIG. 5) does not need to include a logarithm / integer conversion unit in front of the variable gain amplifier 105, and can greatly reduce the circuit scale.

  Next, the case where the high frequency power amplifier 106 is out of the range where it can operate as a nonlinear amplifier will be described. FIG. 7 is a diagram illustrating an example of a circuit configuration of the high-frequency power amplifier 106. The high-frequency power amplifier 106 can be composed of a nonlinear amplifier 120 and a parasitic capacitor 121 connected between the input side and the output side of the nonlinear amplifier 120.

  FIG. 8 is a diagram showing the relationship between the power supply voltage and output power of the high-frequency power amplifier 106 when used as a nonlinear amplifier. As shown in FIG. 8, when the output power is large, the square of the power supply voltage is proportional to the output power, but as the power supply voltage is lowered, the output power does not decrease below a certain value. This value is determined by the level of the input signal of the nonlinear amplifier 120 (the level of the output signal of the variable gain amplifier 105) and the leakage power from the input signal determined by the parasitic capacitance 121. Thus, it can be seen that when the power supply voltage of the high-frequency power amplifier 106 becomes extremely small, amplitude modulation with excellent linearity by the power supply voltage becomes difficult due to leakage power from the input of the high-frequency power amplifier 106.

  For this reason, when the transmission power is sufficiently small, the transmission apparatus 200 performs amplitude modulation with excellent linearity in the variable gain amplifier 105 in the preceding stage of the high-frequency power amplifier 106, and the high-frequency power amplifier 106 is used as a linear amplifier. I use it.

  As described above, in the transmission apparatus 200 according to the second embodiment of the present invention, when transmission power is large, amplitude modulation is performed using the high-frequency power amplifier 106 as a nonlinear amplifier, and transmission power is small. Performs amplitude modulation with the variable gain amplifier 105 and uses the high frequency power amplifier 106 as a linear amplifier. As a result, the transmission apparatus 200 can maintain good distortion characteristics and modulation accuracy of the transmission signal regardless of the transmission power range.

  Further, in the transmission device 200, as in the first embodiment, the true / logarithm conversion units 110 and 109 perform the true / logarithm conversion on the amplitude signal S2 and the transmission power control signal S4, and the amplitude signal expressed logarithmically. Since it outputs as S14 and the transmission power control signal S13 expressed logarithmically, the same effect as 1st Embodiment can be acquired.

  The transmitting apparatus 200 logarithmically converts the amplitude signal S2 and the transmission power control signal S4 expressed in the logarithm by the logarithm / logarithm conversion units 110 and 109, but the amplitude signal and the transmission power control signal expressed in the logarithm. Can be directly input to the adder 102 from the amplitude phase separation unit 101 or the control unit (not shown), the circuit scale can be reduced.

  Further, the transmission apparatus 200 may perform amplitude modulation with the variable gain amplifier 105 in the previous stage, even when performing amplitude modulation with the high-frequency power amplifier 106. In this case, since the input power of the high-frequency power amplifier 106 changes according to the instantaneous power of the amplitude signal S2, when the transmission power of the high-frequency power amplifier 106 is desired to be reduced, the input power of the high-frequency power amplifier 106 is also reduced. Therefore, the linear operation range of the high-frequency power amplifier 106 can be widened.

  Further, the variable gain amplifier 105 does not need to have an exponential function as described above. When the input / output relationship of the variable gain amplifier 105 is linear, the transmission apparatus 200 may be provided with a logarithm-integer conversion unit before the variable gain amplifier 105.

  Further, the transmission apparatuses 100 and 200 described above may be configured to select whether or not to perform the true / logarithmic conversion on the amplitude signal S2 and the transmission power control signal S4 in accordance with the range of the transmission power. For example, the transmission apparatuses 100 and 200 may be configured to perform a true-logarithmic conversion on the amplitude signal S2 and the transmission power control signal S4 only when the transmission power is smaller than a certain value.

  Further, the simulation results shown in FIG. 3 and FIG. 4 are for the EDGE modulation signal, but if the amplitude signal is expressed logarithmically, the same effect can be obtained for modulation schemes other than EDGE.

  Moreover, the transmission apparatuses 100 and 200 described above may further include a distortion compensation unit 116 that suppresses distortion of the output signal. The distortion compensator 116 is connected to any position up to the preceding stage of a block that generates distortion (typically, the high-frequency power amplifier 106). The distortion compensator 116 distorts the amplitude signal S7 supplied as a power supply voltage to the high-frequency power amplifier 106 in advance so that at least distortion generated in the high-frequency power amplifier 106 is compensated. FIG. 9A is a block diagram illustrating an example of a configuration of the transmission device 100a including the distortion compensation unit 116. Referring to FIG. 9A, distortion compensator 116 reverses the distortion generated in high-frequency power amplifier 106 to amplitude signal S5 subjected to transmission power control in order to compensate at least the distortion generated in high-frequency power amplifier 106. Give distortion. Typically, the distortion compensation unit 116 is realized by a ROM table or a digital circuit. In the present invention, since the amplitude signal is represented by a log scale, even when the amplitude signal is very small, the quantization error of the amplitude signal is small, and distortion compensation can be performed more accurately.

(Third embodiment)
FIG. 9B is a block diagram illustrating an example of a configuration of a wireless communication device according to the third embodiment of the present invention. With reference to FIG. 9B, a wireless communication apparatus 400 according to the third embodiment includes a transmission circuit 410, a reception circuit 420, an antenna sharing unit 430, and an antenna 440. The transmission circuit 410 is the transmission device according to any one of the first to second aspects described above. The antenna sharing unit 430 transmits the transmission signal output from the transmission circuit 410 to the antenna 440 and prevents the transmission signal from leaking to the reception circuit 420. The antenna sharing unit 430 transmits the reception signal input from the antenna 440 to the reception circuit 420 and prevents the reception signal from leaking to the transmission circuit 410. Therefore, the transmission signal is output from the transmission circuit 410 and emitted from the antenna 440 to the space via the antenna sharing unit 430. The received signal is received by the antenna 440 and received by the receiving circuit 420 via the antenna sharing unit 430.

  The wireless communication apparatus 400 according to the third embodiment uses the transmission apparatus according to the first and second embodiments, thereby preventing degradation of ACLR and EVM even at a low transmission output with a small amplitude signal and power efficiency. Can be improved. Therefore, it is possible to provide a wireless communication apparatus that can transmit and receive high-quality signals and that has improved power efficiency. In addition, since there is no branch such as a directional coupler in the output of the transmission circuit 410, loss from the transmission circuit 410 to the antenna 440 can be reduced, power consumption during transmission can be reduced, and wireless As a communication device, it can be used for a long time. Note that the wireless communication device 400 may be configured to include only the transmission circuit 210 and the antenna 240.

  Although the present invention has been described in detail above, the above description is merely illustrative of the present invention in all respects and is not intended to limit the scope thereof. It goes without saying that various improvements and modifications can be made without departing from the scope of the present invention.

  The transmission device according to the present invention can be applied to a wireless communication device such as a mobile phone or a wireless LAN.

The block diagram which shows an example of schematic structure of the polar modulation transmission apparatus 100 which concerns on the 1st Embodiment of this invention. The figure which shows the difference in the change range of amplitude signal S5 by the magnitude of transmission power The figure which shows the result of having simulated the influence which quantization noise has on ACLR The figure which shows the result of having simulated the influence which quantization noise has on EVM The block diagram which shows an example of schematic structure of the polar modulation transmission apparatus 200 which concerns on the 2nd Embodiment of this invention. The figure which shows an example of the circuit structure of a variable gain amplifier The figure which shows an example of the circuit structure of the high frequency power amplifier 106 The figure which shows the relationship between the power supply voltage and output electric power of the high frequency power amplifier 106 at the time of using as a nonlinear amplifier FIG. 2 is a block diagram illustrating an example of a configuration of a transmission device 100a including a distortion compensation unit 116. The block diagram which shows an example of a structure of the radio | wireless communication apparatus which concerns on the 3rd Embodiment of this invention. Diagram explaining the outline of polar modulation system The figure which shows an example of the functional block of the conventional transmitter 500 The figure which shows the difference in the change range of amplitude signal S55 by the magnitude of transmission power The figure which shows the result of having simulated the influence which quantization noise has on ACLR The figure which shows the result of having simulated the influence which quantization noise has on EVM

Explanation of symbols

100, 200 Transmitting apparatus 101 Amplitude phase separation unit 102, 114-115 Adder 103 Amplitude signal amplifier 104 Phase modulation unit 105 Variable gain amplifier 106 High frequency power amplifier 107, 108 D / A converter 109, 110 True-logarithm conversion unit 112, 113 Switch 116 Distortion Compensation Unit 120 Nonlinear Amplifier 121 Parasitic Capacitance 400 Wireless Communication Device 410 Transmission Circuit 420 Reception Circuit 430 Antenna Sharing Unit 440 Antenna

Claims (11)

A polar modulation transmitter,
An amplitude phase separation unit for separating the modulation baseband signal into an amplitude signal and a phase signal;
A first logarithm / logarithm conversion unit that performs logarithm / logarithm conversion on the amplitude signal and outputs the logarithmically expressed amplitude signal;
A second logarithm / logarithm conversion unit that performs logarithm / logarithm conversion on the transmission power control signal and outputs the logarithmically expressed transmission power control signal;
An adder that adds the logarithmically expressed transmission power control signal to the logarithmically expressed amplitude signal and outputs the resultant signal as a transmission power controlled amplitude signal;
A logarithm / logarithm conversion unit for logarithm / logarithm conversion of the transmission power controlled amplitude signal and outputting as an amplitude signal expressed as a logarithm;
A phase modulation unit that performs phase modulation on a high-frequency carrier signal based on the phase signal and outputs the signal as a high-frequency phase modulation signal;
A high-frequency power amplifier that performs amplitude modulation on the high-frequency phase modulation signal based on a supplied power supply voltage and outputs the high-frequency transmission signal;
A polar modulation transmission apparatus comprising: an amplitude signal amplifier that amplifies the amplitude signal expressed as a true number and supplies the amplified amplitude signal to the high-frequency power amplifier as a power supply voltage.   2. The polar according to claim 1, wherein the high-frequency power amplifier operates as a nonlinear amplifier, and performs amplitude modulation on the high-frequency phase modulation signal according to the transmission power control signal and the amplitude signal. Modulation transmitter.   The polar modulation transmission apparatus according to claim 1, further comprising a variable gain amplifier that amplifies the high-frequency phase modulation signal with a controlled gain after the phase modulation unit.   The polar modulation transmission apparatus according to claim 1, wherein the amplitude signal amplifier includes a switching regulator or a class D amplifier. A second adder for adjusting transmission power is further provided between the adder and the logarithm / integer conversion unit,
The polar modulation transmission apparatus according to claim 1, wherein the second adder adds a gain adjustment value to the power-controlled amplitude signal. The amplitude signal amplifier selectively supplies a power voltage corresponding to the amplitude signal and the transmission power control signal to the high-frequency power amplifier, or a predetermined fixed value power voltage,
When a power supply voltage corresponding to the amplitude signal and the transmission power control signal is selected, the high frequency power amplifier operates as a nonlinear amplifier, and for the high frequency phase modulation signal amplified by the variable gain amplifier, Amplitude modulation according to the transmission power control signal and the amplitude signal, to output as a high frequency transmission signal,
When the predetermined fixed value power supply voltage is selected,
The variable gain amplifier performs amplitude modulation according to the transmission power control signal and the amplitude signal on the high-frequency phase modulation signal output from the phase modulation unit,
The polar modulation transmission apparatus according to claim 3, wherein the high-frequency power amplifier operates as a linear amplifier, amplifies the signal subjected to amplitude modulation by the variable gain amplifier, and outputs the amplified signal as a high-frequency transmission signal. A third adder for adjusting transmission power is further provided between the adder and the variable gain amplifier,
The polar modulation transmission apparatus according to claim 6, wherein the third adder adds a gain adjustment value to the power-controlled amplitude signal. A D / A converter is further provided at any position up to the previous stage of the logarithm / integer conversion unit,
The polar modulation transmission apparatus according to claim 1, wherein an analog signal via the D / A converter is input to the logarithm / integer conversion unit.   A distortion that is connected to any position up to the preceding stage of the high-frequency power amplifier and that predistorts the amplitude signal supplied as a power supply voltage to the high-frequency power amplifier so that at least distortion generated in the high-frequency power amplifier is suppressed. The polar modulation transmission apparatus according to claim 1, further comprising a compensation unit. A wireless communication device,
A transmission circuit for generating a transmission signal;
An antenna for outputting a transmission signal generated by the transmission circuit;
The radio communication apparatus according to claim 1, wherein the polar modulation transmission apparatus according to claim 1 is used for the transmission circuit. A receiving circuit for processing a received signal received from the antenna;
The radio according to claim 9, further comprising: an antenna sharing unit that outputs a transmission signal generated by the transmission circuit to the antenna and outputs a reception signal received from the antenna to the reception circuit. Communication device.

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