JP4535640B2 - Aperture antenna and substrate with aperture antenna - Google Patents

Description

【００４９】
【表２】

【００５０】
図１乃至図３の構造の開口面アンテナにおいては、導波管型給電線路２に１つの誘電体共振器１を搭載させたものであったが、導波管型給電線路２上に、複数の誘電体共振器１を所定の間隔をもって搭載させるととともに、図１乃至図３と同様にして結合孔３２によって開口面を有する各誘電体共振器１と導波管型給電線路２とを結合させることによって、直列給電アンテナを形成することができる。
【００５１】
図６は、その直列給電アンテナの一例を示す斜視図である。図６において、図１乃至図２に示したものと同様の個所には同じ符号を付してある。図中、６は複数の導波管型給電線路２群に給電するための導波管型第２給電線路であり、６１は前記導波管型第２給電線路６と導波管型給電線路２とを結合するためのスロットであり（図面では、説明の便宜上、導波管型給電線路２の半分を省略した。）６２は前記導波管型第２給電線路６の端部に作られたアンテナポートである。
【００５２】
この図において、アンテナポート６２より入力された高周波信号は、分岐を繰り返し、スロット６１群で６つの導波管型給電線路２群の長手方向中央で給電される。導波管型給電線路２の長手方向中央で結合された高周波信号は左右に分岐し、導波管型給電線路２上に配置された５個（左右で計１０個）の誘電体共振器１群と結合する。その後、誘電体共振器１の開口部３１から、直線偏波または円偏波が放射される。
【００５３】
この場合、放射パターンを制御するために、各誘電体共振器１と導波管型給電線路２との結合量を調整する必要がある。この調整は、結合孔３２のサイズ、誘電体共振器１上部の開口部３１の径、または誘電体共振器１の径ｄを変えることにより適宜調整することができる。
【００５４】
また、本発明によれば、多層構造からなる誘電体基板に対して、上記の導波管型給電線路２と誘電体共振器１とを多層配線技術における導体パターンと垂直導体を組み合わせることによって、誘電体導波管構造体および誘電体共振器構造体を形成して、多層配線基板の内部に上記の開口面アンテナを内蔵させることができる。
【００５５】
図７は、図１の開口面アンテナを誘電体基板内に形成した開口面アンテナ付き基板（以下、単にアンテナ基板という。）の一例を示すもので、（ａ）は平面図、（ｂ）は（ａ）のＡ１−Ｂ１線断面図である。なお、図１乃至図２に示したものと同様の個所には同じ符号を付してある。図７のアンテナ基板において、共振器部誘電体層５１ａ、５１ｂを積層してなる共振器部誘電体基板５１が形成され、この共振器部誘電体基板５１の最上面には共振器部上部主導体層１１が、また下面には共振器部下部主導体層１３がそれぞれ形成されており、共振器部誘電体基板５１は両共振器部主導体層１１、１３により挟持されている。
【００５６】
また、上部主導体層１１には、導体が形成されていない開口部３１が形成されている。また、この開口部３１周辺には、所定間隔を持って共振器部上部主導体層１１および共振器部下部主導体層１３間を電気的に接続するように複数の共振器部貫通導体１４が形成されている。この複数の共振器部貫通導体１４は、高周波信号の信号波長の２分の１未満の繰り返し間隔で配設されている。なお、この繰り返し間隔は、必ずしも一定の値であることに限られず、信号波長の２分の１未満で種々の値を組合わせて設定しても良い。また、２重、３重と配設されても良い。この複数の貫通導体１４群によって電磁波遮蔽体が形成され、これが図１の誘電体共振器の導体壁１ｂを疑似的に形成している。
【００５７】
また、この複数の貫通導体１４は、上部主導体層１１と下部主導体層１３間において該主導体層と平行に設けられた共振器部副導体層１２によって電気的に接続されている。この共振器部副導体層１２には開口部３１と相似形状の導体非形成部を設け、単層または必要に応じて複数層形成されて、複数の共振器部貫通導体１４と共に共振器部誘電体基板５１内に格子状の共振器部導体側壁１ｂを形成する。
【００５８】
そして、共振器部上部主導体層１１、共振器部下部主導体層１３、複数の共振器部貫通導体１４および共振器部副導体層１２から成る共振器導体壁で囲まれ、誘電体で満たされた空間により、共振器部誘電体基板５１内に、誘電体共振器１構造体を形成している。
【００５９】
一方、共振器部誘電体基板５１の下面には、給電部誘電体層５２ａ、５２ｂを積層して成る給電部誘電体基板５２が形成されており、給電部誘電体基板５２の上面には給電部上部主導体層２１が形成され、下面には給電部下部主導体層２３が形成されており、給電部誘電体基板５２は両給電部主導体層２１、２３により挟持されている。なお、図中では、共振器部下部主導体層１３と給電部上部主導体層２１とは一体化されている。
【００６０】
また、給電部上部主導体層２１および給電部下部主導体層２３の間には、両者を電気的に接続するように複数の給電部貫通導体２４ａ、２４ｂが２列に配設されている。この複数の貫通導体２４ａ、２４ｂは、高周波信号の信号波長の２分の１未満の繰り返し間隔で配設されている。なお、この繰り返し間隔は、必ずしも一定の値であることに限られず、信号波長の２分の１未満で種々の値を組合わせて設定しても良い。また、２重、３重と配設されても良い。また、この複数の貫通導体２４ａ、２４ｂは、上部主導体層２１と下部主導体層２３間において該主導体層と平行に設けられた給電部副導体層２２によって電気的に接続されている。
【００６１】
この複数の貫通導体２４ａ、２４ｂおよび副導体層２２によって電磁波遮蔽体が形成され、これが図１の給電線路２のＥ面導体を疑似的に形成している。
【００６２】
そして、給電線路部上部主導体層２１、給電線路部下部主導体層２３、複数の給電線路部貫通導体２４ａ、２４ｂおよび副導体層２２から成る疑似的導体壁とで囲まれ、誘電体で満たされた空間により、断面が矩形状の誘電体導波管からなる給電線路構造体２を形成している。
【００６３】
特に、この誘電体導波管をシングルモードで用いる場合には、給電部貫通導体群２４ａと２４ｂとの間隔ｗは、λ／２＜ｗ＜λで配設される。なお、給電部誘電体層５２は単層であっても良く、この場合には、給電部副導体層２２は形成されない。
【００６４】
そして、この共振器部下部主導体層１３（給電部上部主導体層２１）には、誘電体共振器構造体１と、導波管型給電線路構造体２を結合するために、非導体形成部を形成して楕円形状の結合孔３２を形成することによって、上記誘電体共振器構造体１と導波管型給電線路構造体２とが結合されている。
【００６５】
そして、導波管型給電線路２から結合孔３２を通して開口部３１側に放射された高周波信号の電磁波は、誘電体共振器１があることにより、その空間より外側の一対の主導体層１１、１３間を伝播することなく、開口部３１から自由空間に放射される。
【００６６】
図８（ａ）は、図７のアンテナ基板において、反射抑制構造が付加された開口面アンテナを誘電体基板内に形成したアンテナ基板の一例を示すもので、（ａ）は平面図、（ｂ）は（ａ）のＡ２−Ｂ２線断面図である。図１及び図２に示したものと同様の個所には同じ符号を付してある。
【００６７】
図８においては、導波管型給電線路構造体２の導波管内側に給電部副導体層２２を一部延設して水平導体４２が設けられ、その水平導体の端部は、垂直導体４１によって、主導体層２３と電気的に接続されている。このようにして、反射抑制垂直導体４１と反射抑制水平導体４２とから、反射抑制構造４が導波管型給電線路構造体２内に形成されている。
【００６８】
なお、図８に示す本発明の実施形態の一例では、反射抑制垂直導体４１は給電部誘電体層５２ｂのみに形成されているが、給電部誘電体層５２ａに形成しても良く、また、導波管型給電線路２が多数の誘電体層で形成されている場合はその複数の層に形成しても良い。
【００６９】
なお、このアンテナ基板は、前述したように、結合孔３２の形成箇所によって図４に示した直線偏波を放射するアンテナ基板、図５に示した円偏波を放射するアンテナ基板として機能させることができる。また、複数の誘電体共振器構造体１を導波管型給電線路構造体２に対して所定の間隔で配列することによって、直列給電アンテナ基板を形成することもできる。
【００７０】
また、本発明によれば、図７、図８に示したように、多層構造の誘電体基板内部に開口面アンテナを形成することによって、アンテナ基板の他の部分に種々の回路を形成することができる。
【００７１】
図９は、本発明の直列給電アンテナ基板の裏面に能動素子を実装した場合の一例を示すもので、（ａ）は斜視図、（ｂ）は（ａ）のＡ３−Ｂ３断面図である。図中、８１はアンテナポート６２と表面回路とを結合する接続部、７１は信号増幅器、７２はフィルター、７３はミキサ、７４は高周波信号発生器、８２はＩＦ信号のＩＦポートである。
【００７２】
例えば、ＩＦポート８２から入力されたＩＦ信号は高周波信号発生器７４で生成された搬送信号とミキサ７３でミキシングされ、フィルター７２で帯域外の高調波等の高周波成分がカットされた後、信号増幅器７１で増幅され、接続部８１を介してアンテナ基板に入力される。７１〜７４の全ての能動素子がアンテナ基板５に実装される必要はないが、少なくとも信号増幅器７１がアンテナ基板５に実装されたアンテナモジュールの形態は、特に信号波長がミリ波帯を用いる場合、伝送損失の観点でメリットが大きい。
【００７３】
図１０は、本発明の直列給電アンテナ基板の裏面に能動素子を実装した他の例を示すもので、（ａ）は斜視図、（ｂ）は、（ａ）のＡ４−Ｂ４断面図である。図９に示したものと同様の個所には同じ符号を付してある。７５はスイッチまたはサーキュレータまたはダイプレクサ等の信号切替え器、８２ａはＩＦ入力ポート、８２ｂはＩＦ出力ポートである。
【００７４】
ＩＦ入力ポート８２ａから入力されたＩＦ信号は高周波信号発生器７４で生成された搬送信号とミキサ７３ａでミキシングされ、フィルター７２ａで帯域外の高調波等の高周波成分がカットされた後、高出力信号増幅器７１ａで増幅され、スイッチやサーキュレータまたはダイプレクサ等の信号切り替え器７５により、接続部８１方向のみに信号が送られ、アンテナ基板５に入力される。一方、アンテナ基板５で受信して接続部８１に到達した信号は、信号切り替え器７５により、低雑音信号増幅器７１ｂのみに信号が送られ、フィルター７２ｂで帯域外の信号をカットされた後、高周波信号発生器７４で生成された信号とキクサ７３ｂでミキシングされ、ＩＦ信号のみ取り出される。その後、ＩＦ出力ポート８２ｂより出力される。このように、信号切り替え器７５を配設することにより、送受共用のアンテナ基板を提供することができる。
【００７５】
図１１は、本発明直列給電のアンテナ基板の裏面に半導体素子をキャビティ内に実装した形態の一例を示すもので、（ａ）は斜視図であり、（ｂ）は（ａ）のＡ５−Ｂ５断面図である。図１０に示したものと同様の個所には同じ符号を付してある。７は半導体素子、９はキャビティである。
【００７６】
半導体素子７はスイッチまたは信号増幅器等の単一機能を持つものであっても、図９または図１０に示した機能素子群を集積化したものであっても良い。
【００７７】
このように、アンテナ基板５裏面にキャビティ９を形成することにより、キャビティ９内に半導体素子７を収納することができるので、特性が高く、低コストのアンテナ基板５が実現できる。
【００７８】
以上のアンテナ基板における誘電体基板は、適当な厚みの誘電体層を積層することによって容易に形成することができる。また、導体層は、導体ペーストの印刷や、導体箔などによって形成でき、また垂直導体は、誘電体層に貫通孔を形成しスクリーン印刷などによって導体ペーストを充填することによって容易に形成することができる。特に、誘電体材料として、銅、銀、金等の低抵抗の導体を用いるために、誘電体基板は、１０５０℃以下で焼成可能な公知の低温焼成セラミック材料、例えば、ホウケイ酸系ガラス、あるいはホウ珪酸系ガラスとＳｉＯ₂、Ａｌ₂Ｏ₃などのセラミックフィラーとを混合した材料等によって形成することによって、伝送損失が小さくなりアンテナ特性が向上する。
【００７９】
【実施例】
次に、本発明の開口面アンテナの具体例について説明する。
図１２は、図８の反射抑制構造を有するアンテナ基板の反射抑制構造の効果を示す図である。図８の誘電体基板５１、５２には、比誘電率４．９のガラスセラミックスを用い、誘電体共振器１の厚みを０．６ｍｍ、導波管型給電線路２のサイズを（ｗ、ｈ）＝（１．８２ｍｍ、０．６ｍｍ）、結合孔３２の中心位置は導波管型給電線路２の中心軸からのずれ量ｃ＝０．３９ｍｍとした。また周波数は、６２．５ＧＨｚにて評価した。
【００８０】
図１２（ａ）は結合孔３２を楕円形状とし、そのサイズａ（楕円の長軸、短軸はｂ＝１．４４ａ−０．５２とした）を変化させたときの反射特性である。誘電体共振器１径ｄおよび開口部サイズはφ２．１２ｍｍとした。
【００８１】
反射抑制構造としては、図８における結合孔３２の下側に、幅０．２ｍｍ、長さ０．６７ｍｍの水平導体４２を導波管型給電線路の０．３ｍｍの厚みの位置に副導体層２２より延設し、水平導体４２の端部には直径が０．２ｍｍの垂直導体４１が下側の主導体層（Ｅ面導体）２３まで伸びた構造を導波管型給電線路２内部に左右対称に形成した。
【００８２】
図の●は反射抑制構造４を付加した場合、△は反射抑制構造４のない場合の結果である。反射抑制構造４がない場合、反射は−２０ｄＢより大きいのに対し、反射抑制構造４がある場合は、反射が−３０ｄＢ以下に抑制されていることがわかる。
【００８３】
図１２（ｂ）は、誘電体共振器１の径ｄを変化させたときの反射特性を示す図である。楕円形結合孔３２のサイズはａ＝１．０００ｍｍ、ｂ＝０．９１４ｍｍとし、反射抑制構造４は図１２（ａ）の場合と同じにした。なお、開口部３１のサイズは誘電体共振器１の径ｄと同じにした。図の●は反射抑制構造４を付加した場合、△は反射抑制構造４のない場合の結果である。反射抑制構造４がない場合、反射は−２０ｄＢより大きいのに対し、反射抑制構造４がある場合は、反射が−３０ｄＢ以下に抑制されていることがわかる。
【００８４】
図１３は、開口面アンテナを用いて、円偏波または直線偏波を放射させた例を示すアンテナの放射パターンである。図の横軸はアンテナ面法線方向からの角度であり、縦軸は電磁波の相対強度を示す。また、実線は右旋円偏波成分、破線は左旋円偏波成分を示す。なお、評価は６２．５ＧＨｚで行った。
【００８５】
誘電体層には，比誘電率４．９のガラスセラミックスを用い、誘電体共振器１の径ｄおよび開口部３１のサイズをφ２．１２ｍｍ、誘電体共振器１の厚みを０．６ｍｍ、楕円形結合孔３２のサイズはａ＝１．０００ｍｍ、ｂ＝０．９１４ｍｍ、導波管型給電線路２のサイズは（ｗ、ｈ）＝（１．８２ｍｍ、０．６ｍｍ）とした。また、図１２で形成した構造と全く同じ構造の反射抑制構造を形成した。
【００８６】
図１３（ａ）は、楕円形結合孔３２の中心位置の導波管型給電線路２の中心軸からのずれ量ｃ＝０．３９ｍｍとした本発明の開口面アンテナの結果を示すグラフである。この場合、法線方向（０°方向）の左旋円偏波成分は−３０ｄＢ以下で、ほとんどが右旋円偏波成分である。即ち、きれいな右旋円偏波の電磁波が放射されていることがわかる。
【００８７】
図１３（ｂ）は、楕円形結合孔３２の中心位置は導波管型給電線路２の中心とした場合の結果を示すグラフである。この場合、実線の右旋円偏波成分と破線の左旋円偏波成分とが一致している。即ち、きれいな直線偏波の電磁波が放射されていることがわかる。
【００８８】
図１４（ａ）は結合孔サイズと放射量および円偏波の軸比の関係を示す図であり、図１４（ｂ）は周波数に対する軸比の変化を示す図である。
【００８９】
誘電体基板５１、５２には比誘電率４．９の材料を用い、誘電体共振器１の厚みｔを０．６ｍｍ、誘電体共振器１の径ｄおよび開口部３１のサイズはφ２．１２ｍｍ、導波管型給電線路２のサイズを（ｗ、ｈ）＝（１．８２ｍｍ、０．６ｍｍ）とした。楕円形結合孔３２の中心位置の導波管型給電線路２の中心軸からのずれ量ｃ＝０．３９ｍｍとした。また、図１２で形成した構造と全く同じ構造の反射抑制構造を形成した。
【００９０】
図１４（ａ）は楕円形結合孔３２サイズａ（楕円の長軸、短軸はｂ＝１．４４ａ−０．５２とした）を変化させたときの放射量と軸比の関係を示した図であり、周波数は６２．５ＧＨｚで評価したものである。
【００９１】
また、図中の●は放射量、□は円偏波における軸比を示している。この図から、楕円型結合孔サイズを０．８６ｍｍから１．０２ｍｍまで変化させることにより、放射量を１０〜６０％へと制御できると共に、そのときの軸比も３ｄＢ以内の良好な特性が得られることがわかる。
【００９２】
図１４（ｂ）は、楕円型結合孔３２のサイズをａ＝１．０２０ｍｍとしたときの、軸比の周波数依存性を示す図である。この図から、周波数が５５〜６５ＧＨｚと１０ＧＨｚ変化させても、軸比の変化は約１ｄＢ以下で小さいことがわかる。
このことは、寸法精度が変化しても軸比の変化は非常に小さいことを意味している。
【００９３】
図１５（ａ）は、開口部３１のサイズと放射量および円偏波の軸比の関係を示す図であり、図１５（ｂ）は誘電体共振器１の径ｄと放射量および円偏波の軸比の関係を示す図である。
【００９４】
誘電体基板５１、５２には、比誘電率４．９のガラスセラミックスを用い、誘電体共振器１の厚みｔを０．６ｍｍ、導波管型給電線路２のサイズを（ｗ、ｈ）＝（１．８２ｍｍ、０．６ｍｍ）とした。楕円形結合孔３２の中心位置の導波管型給電線路２の中心軸からのずれ量ｃ＝０．３９ｍｍとした。また、図１２で形成した構造と全く同じ構造の反射抑制構造を形成した。
【００９５】
図１５（ａ）は開口部３１のサイズｄを変化させたときの放射量と軸比の関係を示した図であり、周波数は６２．５ＧＨｚで評価したものである。なお、誘電体共振器１の径は２．１２ｍｍで一定である。また、図中の●は放射量、□は円偏波における軸比を示している。この図から、開口部サイズを１．５ｍｍから２．２ｍｍまで変化させることにより、放射量を１０〜６０％へと制御できると共に、そのときの軸比も約２ｄＢ以内の良好な特性が得られることがわかる。
【００９６】
図１５（ｂ）は誘電体共振器１の径を変化させたときの放射量と軸比の関係を示した図であり、周波数は６２．５ＧＨｚで評価したものである。なお、開口部３１のサイズは誘電体共振器１の径と同じにした。また、図中の●は放射量、□は円偏波における軸比を示している。この図から、共振器径を１．５ｍｍから２．２ｍｍまで変化させることにより、放射量を２〜６０％へと制御できると共に、そのときの軸比も約１．５ｄＢ以内の良好な特性が得られることがわかる。
【００９７】
図１６は図６に示す直列給電方式による、放射パターン制御の一例を示す図である。この場合（図６参照）、直列給電導波管型給電線路２はスロット６１により中央で給電されており、分岐後、左右に並ぶ５つの誘電体共振器１の放射量は対称とした。このとき、中央から端部に向かう誘電体共振器１からの放射量を前述したように結合孔サイズ、開口部サイズ、共振器サイズを変えて４２％、５２％、５８％、６０％、６２％とした。またアンテナ素子間隔は自由空間波長をλ₀としたとき、５．２５λ₀とした。図１６に示すように、この場合、サイドローブレベルが−２５ｄＢ以下に制御されていることがわかる。
【００９８】
【発明の効果】
以上詳述した通り、本発明の開口面アンテナによれば、楕円形状の結合孔と誘電体共振器とにより共振周波数を制御できるため、結合孔の寸法精度に数％の誤差があったとしても、安定して所望の周波数帯における共振を得ることができ、それにより開口面から放射される高周波信号の電磁波を安定して放射させることができるものとなる。また、給電線路での不要放射がなく、伝送損失も小さいことからアンテナでの損失を小さいものとすることができるとともに、楕円型状結合孔と誘電体導波管との位置関係を調整することにより、右旋円偏波、左旋円偏波を放射させることができるものとなる。
【００９９】
また、前記導波管または誘電体導波管内の結合孔の下部に位置する導波管または誘電体導波管内に、反射を抑制する構造を形成することによってアンテナ素子結合部でのインピーダンスのずれによる反射波を十分抑制できるものとなる。さらに、直列給電の場合でも反射波を十分抑制できるので、アンテナ素子を誘電体導波管の概ね１管内波長間隔として、放射ビームをアンテナ面の法線方向に設定しても、反射損失を低く抑えることができるものとなる。
【０１００】
またさらに、積層型開口面アンテナの楕円形状の結合孔、誘電体共振器の円形状の開口部、誘電体共振器の径の大きさを変えることにより放射量を調整してなることとしたことから、放射パターンを容易に制御できるとともに、円偏波の場合でも、軸比を小さく抑えることができるものとなる。
【０１０１】
またさらに、誘電体基板内に、高周波信号を伝送可能な誘電体導波管と、円柱型誘電体の側面の全部または一部が金属で覆われ、かつ高周波信号を空間に放射するための開口部を有する円柱型誘電体共振器とが形成され，誘電体導波管のＨ面導体内の前記円柱型誘電体共振器の開口部の中心と対向する位置に結合孔を形成し、該結合孔を介して高周波信号を前記誘電体導波管から円柱型誘電体共振器に給電してなるものとしたことにより、誘電体基板の裏面に能動素子や信号切り替え器を直接実装またはキャビティを形成しその中に内蔵することが可能となり、小型で信頼性が高く、低コストのアンテナ基板とする事ができる。
【図面の簡単な説明】
【図１】 本発明の開口面アンテナの一例を示す概略斜視図である。
【図２】 （ａ）は本発明の反射抑制構造を有する開口面アンテナの一例を示す概略斜視図であり、（ｂ）は（ａ）のｘ−ｘ断面図である。
【図３】 開口面アンテナの結合孔の形状の例を示す図である。
【図４】 （ａ）は直線偏波を放射させる積層型開口面アンテナの一例を示す平面図であり、（ｂ）は磁界分布を示す図である。
【図５】 （ａ）は本発明における円偏波を放射させる積層型開口面アンテナの一例を示す平面図であり、（ｂ）は磁界分布を示す図である。
【図６】 本発明の開口面アンテナを用いた直列給電アンテナの一例を示す分解図である。
【図７】 （ａ）は本発明の開口面アンテナ付き基板の一例を示す平面図であり、（ｂ）は（ａ）のＡ１−Ｂ１断面図である。
【図８】 （ａ）は本発明の反射抑制構造を有する開口面アンテナ付き基板の一例を示す平面図であり、（ｂ）は（ａ）のＡ２−Ｂ２断面図である。
【図９】 （ａ）は本発明の開口面アンテナ付き基板に能動素子群を実装した一例を示す斜視図であり、（ｂ）は（ａ）のＡ３−Ｂ３断面図である。
【図１０】 （ａ）は本発明の開口面アンテナ付き基板に能動素子群を実装し、送受信共用とした一例を示す斜視図であり、（ｂ）は（ａ）のＡ４−Ｂ４断面図である。
【図１１】 （ａ）は本発明の開口面アンテナ付き基板にキャビティを形成した一例を示す斜視図であり、（ｂ）は（ａ）のＡ５−Ｂ５断面図である。
【図１２】 本発明の開口面アンテナにおける反射抑制構造の効果を示す図であり、（ａ）は結合孔サイズを変化させたときの特性、（ｂ）は共振器径を変化させた時の特性である。
【図１３】 （ａ）は本発明の開口面アンテナから放射される電磁波が円偏波であることを示す放射パターンであり、（ｂ）は放射される電磁波が直線偏波である場合の放射パターンを示す図である。
【図１４】 （ａ）は本発明の開口面アンテナにおける結合孔サイズと放射量および円偏波の軸比との関係を示す図であり、（ｂ）は周波数に対する軸比の変化を示す図である。
【図１５】 （ａ）は本発明の開口面アンテナにおける開口部サイズと放射量および円偏波の軸比との関係を示す図であり、（ｂ）は共振器径と放射量および円偏波の軸比の関係を示す図である。
【図１６】 本発明の開口面アンテナにおける、直列給電方式による放射パターン制御の一例を示す図である。
【符号の説明】
１ 誘電体共振器
１１ 共振器部上部主導体層
１２ 共振器部副導体層
１３ 共振器部下部主導体層
１４ 共振器部貫通導体
２ 導波管型給電線路
２１ 給電部上部主導体層
２２ 給電部副導体層
２３ 給電部下部主導体層
２４ 給電部貫通導体
３１ 開口部
３２ 結合孔
４ 反射抑制構造
４１ 反射抑制垂直導体
４２ 反射抑制水平導体
５ アンテナ付き基板
５１ 共振器部誘電体基板
５２ 給電部誘電体基板[0001]
BACKGROUND OF THE INVENTION
The present invention relates to an aperture antenna suitable for wireless communication using a high-frequency signal such as a millimeter wave band, and more particularly to an aperture antenna for series feeding and a substrate with an aperture antenna incorporating the same.
[0002]
[Prior art]
Examples of antenna elements that emit radio waves of high-frequency signals such as millimeter waves include slot antennas and patch antennas. These are widely used because of their simple structure, and those using a microstrip line, a waveguide line or the like as a feeder line have been proposed.
[0003]
In addition, there are two types of array antenna feeding systems in which a plurality of antenna elements are arranged. Parallel feeding and series feeding systems are available. However, since the transmission loss of the feeding line becomes a problem as the frequency increases, the series feeding system is often used. Is adopted. In the case of the parallel feeding method, the slot and patch antenna elements are set to the resonance size so that the maximum radiation can be obtained, but in the case of the series feeding method, electromagnetic waves are gradually generated from the feeding end side. In order to radiate, the amount of radiation is adjusted by setting slots and patches smaller than the resonance size.
[0004]
Furthermore, as polarization technology, there are linear polarization and circular polarization. In the case of a wireless communication apparatus, a circular polarization antenna is often used in order to suppress the influence of a reflected wave from a wall or the like. This is because, in the case of linearly polarized waves, the reflected waves are picked up properly, whereas in the case of circularly polarized waves, for example, when radiating right-handed circularly polarized waves, the reflected waves become left-handed circularly polarized waves. This is because the primary reflected wave from the wall or the like is not picked up.
[0005]
The slot antenna is realized, for example, by forming a slot in a conductor wall of a waveguide type feed line in a direction parallel to and orthogonal to the traveling direction of electromagnetic waves. The patch antenna is realized by a rectangular or elliptical patch.
[0006]
Recently, it has been studied to manufacture these antennas with a ceramic substrate. Conventionally, in order to obtain good antenna characteristics, a resin substrate having a low relative dielectric constant has been used. However, since the thermal expansion coefficient of the substrate is large, a package in which MMIC or the like is sealed cannot be directly mounted. , Which led to increased costs.
[0007]
On the other hand, by making the antenna with a ceramic substrate with low thermal expansion, it becomes possible to store the semiconductor element in the cavity where the package etc. are directly mounted or formed, and high reliability and cost reduction are possible. It becomes.
[0008]
[Problems to be solved by the invention]
However, in the case of a slot antenna or a patch antenna, since the frequency band is generally narrow, the dimensional accuracy in manufacturing is severe. Particularly in the millimeter wave band, the antenna size is too small to be manufactured. For example, in order to radiate an electromagnetic wave at a desired frequency to the slot antenna, the dimensional accuracy of the slot needs to be within 1%. In the method of forming the slot on the dielectric substrate by the thick film printing method, the dimension There was a problem that it was difficult to satisfy the accuracy.
[0009]
On the other hand, as disclosed in Japanese Patent Laid-Open No. 11-239017, the inventor uses a spatial resonator as an antenna element, and performs coupling between this element and a feed line in a predetermined slot, thereby providing an antenna element. The dimensional accuracy required for the slot size is relaxed. However, since the slot width is inevitably as small as 10 μm, when the slot is formed by the thick film printing method, the slot width fluctuates due to the dripping of the conductive ink, resulting in deterioration of characteristics. was there.
[0010]
Further, when a circularly polarized wave is radiated as a high-frequency signal by a slot antenna or a patch antenna, it is necessary to set a frequency at which the axial ratio is within 3 dB as a desired value, but the frequency band within that 3 dB Has a problem that the slots and patches must be formed with very high dimensional accuracy.
[0011]
On the other hand, Japanese Patent Laid-Open No. 2001-69924 proposes a structure in which a spatial resonator and a feed line made of a waveguide are coupled by a cross-shaped slot. According to this structure, the dimensional accuracy can be relaxed more than the dimensional accuracy required for the patch antenna element and the slot size, and the frequency band in which the axial ratio is within 3 dB is improved to about 2.4%. There is a problem that the dimensional accuracy of the cross-shaped slot is lowered due to the dripping of the conductive ink, and the variation is large.
[0012]
Furthermore, in the case of the series feeding method in which the antenna element is a slot antenna or a patch antenna, it is necessary to further reduce the size of the slot or antenna from the resonance length in order to adjust the radiation amount. Not only was there a problem of reflection loss. In general, when an antenna element is formed on a feed line, a change in impedance occurs there and a reflected wave is generated. The interval between the antenna elements of the series feeding system is preferably one propagation wavelength so that the phase of the electromagnetic wave radiated from each antenna element is the same phase. Since all the reflected waves overlap with each other in the same phase, a large reflection loss occurs at the input port portion. In order to avoid this, there is a method of intentionally shifting the antenna element interval from one propagation wavelength to reduce reflection loss. However, this method has a problem that the phase of the electromagnetic wave radiated from each antenna element is shifted, so that the radiation beam is shifted in an oblique direction.
[0013]
  The present invention has been devised to solve such conventional problems, and its purpose is to obtain good characteristics at a desired frequency even if the dimensional accuracy in manufacturing the antenna is about several percent. In addition, even in the case of a series feeding type antenna, while suppressing reflection loss, even if the antenna is formed with a high dielectric constant substrate such as ceramic, high dimensional accuracy is not required., Small axial ratioCircular polarizationCan radiateAperture antennaandThe object is to provide a substrate with an aperture antenna.
[0014]
[Means for Solving the Problems]
As a result of repeated studies on the above problems, the present inventor has an opening formed in the upper part, the side surface is covered with an electromagnetic shielding material such as a metal wall, and a substantially circular or polygonal coupling hole is formed in the lower part. It was found that an antenna that does not require high dimensional accuracy can be obtained by feeding the formed cylindrical dielectric resonator with a waveguide or a dielectric waveguide. Further, it has been found that by forming a structure that suppresses reflection inside a waveguide or dielectric waveguide that is a feed line, a reflected wave inside the feed line generated by coupling with the antenna can be suppressed. Furthermore, it is possible to easily radiate circularly polarized waves by forming the position of the coupling hole on the central axis of the dielectric waveguide and by forming it at a position shifted from the central axis. I found. Still further, in a series feeding system in which a plurality of cylindrical dielectric resonators are fed by one waveguide or a dielectric waveguide, the size of the coupling hole, the diameter of the opening of the dielectric resonator, the dielectric resonator It has been found that the overall radiation pattern can be controlled by adjusting the diameter and adjusting the radiation amount.
[0015]
Furthermore, by finding that the above-described cylindrical dielectric resonator or dielectric waveguide can be formed into an antenna substrate using a through conductor group or a conductor pattern group, In addition, a functional element such as an amplifier can be directly mounted to enhance the function, or a cavity for housing a semiconductor element can be formed on the back surface to realize an antenna integrated module, and the antenna substrate can be formed from low-temperature fired ceramics. It has been found that an antenna having excellent characteristics can be obtained because a copper or silver conductor layer having low resistance can be used.
[0016]
  That is, in the aperture antenna of the present invention, all or part of the side surface of the cylindrical dielectric is covered with the electromagnetic wave shield.Configured,An opening for radiating high-frequency signals into spaceOn the other handA cylindrical dielectric resonator having,Waveguide or dielectric waveguide for feeding power to the cylindrical dielectric resonatorAndThe cylindrical dielectric resonator is provided on the H-plane conductor surface of the waveguide or dielectric waveguide.The other main surface side ofAnd the waveguide or dielectric waveguideSaidOf the cylindrical dielectric resonator in the H-plane conductor.SaidAt a position facing the center of the openingAn ellipse centered at a position deviated from the central axis of the waveguide or dielectric waveguideShaped coupling holeButFormationHas been, High-frequency signal through the coupling holeButFrom the waveguide or dielectric waveguideSaidFeeding cylindrical dielectric resonatorIsIt is characterized by that.
[0017]
  As a more specific structure, the high-frequency signalSaidFree sky in a dielectricInterwaveWhen the length is λ, the thickness of the cylindrical dielectric resonator is preferably λ / 4 to λ / 2,SaidLocated below the coupling holeSaidWaveguideInsideOrSaidThe characteristics can be improved by forming a structure for suppressing reflection in the dielectric waveguide.
[0019]
  Also,in frontWhen the width of the waveguide or the dielectric waveguide is w, the center of the coupling hole is at a position shifted from w / 8 to 3w / 8 from the central axis of the waveguide or dielectric waveguide. It is desirable.
[0020]
  The elliptical shapeofThe coupling hole has its long axisThe length ofShort axisLength ofAnd the ratio to R(= Short axis length / Long axis length)R is optimally 0.86 to 0.97.
[0021]
  As a modification of the aperture antenna, the waveguide or dielectric waveguideSaidA plurality of the cylindrical dielectric resonators on the H-plane conductor surfaceButMounted with a wavelength interval within one tubeHas been, All by the waveguide or dielectric waveguideSaidSeries feed to cylindrical dielectric resonatorTo beThus, an aperture antenna of a series feed system can be formed. In that case, the size of the coupling hole, the size of the opening of the cylindrical dielectric resonator, and the size of the diameter of the cylindrical dielectric resonator are changed in the plurality of series-fed cylindrical dielectric resonators. By adjusting the amount of radiation, the overall radiation pattern can be controlled.
[0022]
  In addition, the present inventionThe substrate with an aperture antenna isIn a dielectric substrate in which a plurality of dielectric layers are laminated, a dielectric waveguide structure capable of transmitting a high-frequency signal and all or part of the side surface of a cylindrical dielectric are covered with an electromagnetic wave shielding wall.Is composed of,SaidAn opening for radiating high-frequency signals into spaceOn the other handA cylindrical dielectric resonator structure, and the cylindrical dielectric resonator structure on an H-plane conductor of the dielectric waveguide structure.The other mainThe dielectric waveguide structure is arranged so that the surfaces are coupled to each other.SaidOf the cylindrical dielectric resonator structure in the H-plane conductor.SaidAt a position facing the center of the openingAn ellipse centered at a position deviated from the central axis of the dielectric waveguide structureShaped coupling holeButFormationHas beenThrough the coupling holeSaidHigh frequency signalButFrom the dielectric waveguide structureSaidFeeding cylindrical dielectric resonator structureIsIt is characterized by thatYesThus, the aperture antenna can be formed in the multilayer substrate.
[0023]
  In such a substrate, the dielectric waveguide structure isFeeding partUpper main conductor layer andFeeding partThe lower main conductor layer and the predetermined intervalFeeding partUpper main conductor layerandAboveFeeding partLower main conductorLayerMultiple electrically connectingFeeding partThrough conductorWhenElectromagnetic shielding wall consisting ofWithTheOhFurther, the plurality of through conductors areThe power feeding unitUpper main conductor layer andThe power feeding unitLower main conductor layerWithIn between, The feeder main conductor layer and the feeder lower partProvided parallel to the main conductor layerFeeding partElectrically connected by sub conductor layerNoIt is desirable.
[0024]
  The cylindrical dielectric resonator structure is formed on the surface of the dielectric substrate.SaidWith openingResonator partThe upper main conductor layer was formed at a position facing the opening.Resonator partFormed in the lower main conductor layer and in the dielectric substrate around the opening.AndAt a predetermined intervalResonator partUpper main conductor layer and saidResonator partA plurality of electrical connections to the lower main conductor layerResonator partThrough conductors, andResonator partUpper main conductor layer and saidResonator partLower main conductor layerWithIn between, The resonator unit upper main conductor layer and the resonator unit lower partA plurality of the plurality of conductor conductors provided in parallel with the main conductor layerResonator partConnecting through conductors electricallyResonator partAntenna conductor wall composed of sub-conductor layerWithIt is characterized by that.
[0025]
In this substrate, at least one signal amplifier is mounted on the back surface of the dielectric substrate, or at least one selected from the group of a switch, a circulator, and a diplexer is mounted on the back surface of the dielectric substrate. A cavity for housing the semiconductor element can be formed on the back surface of the dielectric substrate.
[0026]
  The dielectric substrateLow materialHot-fired ceramicsInBy,Various conductor layers can be formed of low-resistance metalBecauseSuitable for high-frequency signal transmission.
[0028]
Further, when the waveguide or dielectric waveguide is coupled to a large number of dielectric resonators by the series feeding method, the diameter of each dielectric resonator, the diameter of the opening, or the size of the coupling hole is adjusted. Thus, the amount of radiation can be easily adjusted, so that a desired radiation pattern can be formed. Further, even when the radiation amount of a certain antenna element is large, the reflection loss caused by impedance mismatch can be reduced by the reflection suppressing structure formed in the dielectric waveguide, so that good antenna characteristics can be obtained.
[0029]
Furthermore, the dielectric resonator of the antenna element and the dielectric waveguide of the feeder line are dielectrically formed by using a through conductor group formed on a dielectric substrate having a multilayer structure and a conductor pattern group formed on the surface of the dielectric layer. Since it can be formed in the body substrate, a functional element such as an amplifier is directly mounted on the back surface of the antenna substrate for higher functionality, or a switch, a circulator, or a diplexer is mounted or built into the antenna substrate for transmission and reception. The antenna integrated module can be formed by forming a cavity for housing the semiconductor element on the back surface.
[0030]
Furthermore, by forming the dielectric substrate from low-temperature fired ceramics, conductor patterns, vertical conductors, and the like can be formed from copper or silver conductors with low resistance, so that excellent antenna characteristics can be obtained.
[0031]
DETAILED DESCRIPTION OF THE INVENTION
Hereinafter, an aperture antenna according to the present invention will be described with reference to the drawings. FIG. 1 is a schematic perspective view showing an example of an aperture antenna according to the present invention. In the aperture antenna shown in FIG. 1, reference numeral 1 denotes a dielectric resonator, and 2 denotes a waveguide or dielectric waveguide serving as a feed line (hereinafter referred to as a waveguide feed line).
[0032]
According to the aperture antenna of FIG. 1, the dielectric resonator 1 has a cylindrical dielectric 1a whose side surface is covered with a conductor wall 1b serving as an electromagnetic wave shield, and a high-frequency signal is applied to the top surface of the dielectric resonator 1 in space. A radiating aperture 31 is formed. The dielectric resonator 1 is mounted on the H-plane conductor surface of the waveguide feed line 2. Further, the dielectric resonator 1 and the waveguide feed line 2 are coupled by a coupling hole 32 formed in the H-plane conductor of the waveguide feed line 2 or on the bottom surface of the dielectric resonator 1. Yes.
[0033]
According to the aperture antenna having such a structure, the lowest coupling mode between the coupling hole 32 and the dielectric resonator 1 is such that the conductor wall 1b of the dielectric resonator 1 surrounds the coupling hole 32 in a circular shape as shown in FIG. Therefore, a mode similar to the resonance mode (TE111 or TM111) of the 1/2 dielectric cylindrical resonator is generated in the space filled with the dielectric 1a, and the resonance frequency of the mode is given by the following equation. It will be a thing.
[0034]
f = 150 / ε^1/2× {(m / πd)²+ (1 / 2t)²}^1/2
Here, f: resonance frequency (GHz), d: diameter of dielectric resonator (mm), t: thickness of dielectric resonator (mm), and ε: relative dielectric constant. In the TE111 mode, m = 1.84, and in the TM111 mode, m = 3.83. However, since the cylindrical dielectric resonator 1 is supplied with power through the coupling hole 32, the resonance frequency is affected by the size of the coupling hole 32.
[0035]
  Further, according to the aperture antenna of FIG. 1, the space filled with the dielectric 1a acts as the dielectric resonator 1, so that the free space in the dielectric of the high frequency signal can be obtained.InterwaveWhen the length is λ, the thickness t of the dielectric resonator is preferably set within a range of λ / 4 to λ / 2. That is, if t is smaller than λ / 4, resonance does not occur in the above mode, and if it is larger than λ / 2, another mode is likely to occur, which is not preferable.
[0036]
In the aperture antenna of the present invention, it is desirable to form a structure for suppressing reflection in the waveguide feed line 2 located below the coupling hole 32 of the waveguide feed line 2. 2A and 2B show an example of an aperture antenna to which the reflection suppressing structure of the present invention is added. FIG. 2A is a perspective view, and FIG. 2B is an xx cross-sectional view. In this aperture antenna, the reflection suppressing structure 4 is formed by a vertical conductor 41 and a horizontal conductor 42. The horizontal conductor 42 is disposed so as to narrow the width of the waveguide feed line 2 from both sides, and is electrically connected to the E-plane conductor of the waveguide feed line 2. Further, the horizontal conductor 42 is electrically connected to the lower H-plane conductor of the waveguide feed line 2 by the vertical conductor 41. That is, the horizontal conductor 42 and the vertical conductor 41 are electrically connected to the H-plane conductor and the E-plane conductor of the waveguide feed line 2.
[0037]
In the reflection suppressing structure 4, the high-frequency signal that has propagated through the waveguide feed line 2 is coupled to the dielectric resonator 1 that is an antenna element via the coupling hole 32. Partly reflected. However, the reflection suppressing structure 4 is formed in the waveguide feed line 2 so that the reflected wave from the reflection suppressing structure 4 cancels the reflected wave generated at the coupling portion with the dielectric resonator 1. By setting to, reflection loss can be reduced. That is, the positions of the vertical conductor 41 and the horizontal conductor 42 in the reflection suppressing structure 4 are adjusted so that the reflected wave at the reflection suppressing structure 4 is equal in magnitude and different in phase from the reflected wave at the coupling portion. The amount of reflection at the reflection suppressing structure 4 is adjusted by the position and number of vertical conductors 41 in the waveguide width direction. The phase is adjusted by the distance from the center of the coupling hole 32 in the waveguide axis direction of the vertical conductor 41. That is, increasing the amount of reflection can be realized by bringing the vertical conductor 41 close to the central axis of the waveguide feed line 2 or by forming a plurality of vertical conductors 41.
[0039]
  As a specific shape of the coupling hole 32, as shown in FIG. 3, (a) a circular shape, (b to d) a regular polygon shape having an interior angle smaller than 180 °, (e) an elliptical shape, (f to h) Interior angleButPolygonal shape smaller than 180 ° is mentionedButPolygonal shapes tend to be rounded at the corners when they are formed by printing, etc.. The shape of the coupling hole of the aperture antenna of the present invention,Do not have cornersOvalCircular shape is,It is easy to design, and when it is formed by printing or the like, its shape can be formed with good reproducibility, so that deviation from the design value hardly occurs.
[0040]
  Furthermore, in the aperture antenna of the present invention, the position of the coupling hole 32 that couples the dielectric resonator 1 mounted on the surface of the H-plane conductor of the dielectric resonator 1 is the center of the waveguide feed line 2.AxisBy staggeringCircleIt can radiate polarized waves.
[0041]
4A is a plan view of an aperture antenna that radiates linearly polarized waves, and FIG. 4B is a magnetic field distribution of the electromagnetic waves. In the aperture antenna of FIG. 4, the coupling hole 32 is disposed on the central axis of the waveguide feed line 2. Further, in (b) magnetic field distribution diagram, a broken line arrow indicates the magnetic field distribution of the electromagnetic wave propagating in the waveguide feed line 2, and a solid line arrow indicates the magnetic field coupled to the coupling hole 32.
[0042]
According to FIG. 4B, in the initial state, the magnetic field inside the waveguide feed line 2 coupled to the coupling hole 32 is symmetric, and as a result, does not couple to the coupling hole 32. Thereafter, when the phase advances by 90 °, it is coupled with the magnetic field component on the right with respect to the traveling direction of the electromagnetic field in the waveguide feed line 2. Similarly, when the phase is advanced by 180 °, it is not coupled, and when the phase is advanced by 270 °, it is coupled with the magnetic field component on the left with respect to the traveling direction of the electromagnetic field. In this way, linearly polarized waves are radiated.
[0043]
  FIG. 5A radiates circularly polarized waves.Of the present inventionIt is a top view of an aperture surface antenna, (b) is the magnetic field distribution of the electromagnetic waves. In the aperture antenna shown in FIG. 5, the coupling hole 32 is shifted from the central axis of the waveguide feed line 2 to the left by c with respect to the traveling direction of the electromagnetic wave in the waveguide feed line 2. Is formed. Further, in (b) magnetic field distribution diagram, a broken line arrow indicates a magnetic field distribution of an electromagnetic wave propagating in the waveguide feed line 2, and a solid line arrow indicates a magnetic field coupled to the coupling hole 32.
[0044]
According to FIG. 5B, in the initial state, the coupling hole 32 is coupled with the magnetic field component in the counter-traveling direction of the magnetic field inside the waveguide feed line 2. Thereafter, when the 90 ° phase advances, the magnetic field component on the right side is combined with the traveling direction of the internal electromagnetic field. Similarly, when the phase is advanced by 180 °, it is coupled with the magnetic field of the traveling direction component, and when the phase is advanced by 270 °, it is coupled with the magnetic field component on the left with respect to the traveling direction of the electromagnetic field. In this way, a left-handed circularly polarized wave is radiated.
[0045]
When radiating right-handed circularly polarized light, the coupling hole 32 is formed so as to be shifted from the central axis of the waveguide feed line 2 to the right with respect to the traveling direction of electromagnetic waves in the waveguide feed line 2. Just do it.
[0046]
  Also, when emitting circularly polarized waves, adjustment of the axial ratio is necessary. This is because the coupling hole 32 is formed in an elliptical shape having a major axis length a and a minor axis length b, and the major axis of the elliptical coupling hole 32 isLength ofAnd short axisThe length ofRatio R (=b/a) And the shift amount c from the central axis of the waveguide feed line 2 can be adjusted. If this shift amount c is large, the elliptical coupling hole 32 cannot be formed on the waveguide feed line 2, and if the shift amount c is small, it becomes close to linearly polarized waves. When w is set, the shift amount c is preferably adjusted within the range of w / 8 to 3w / 8.
[0047]
  Tables 1 and 2 show the relationship between the axial ratio in circular polarization and the ratio R between the major axis and the minor axis of the elliptical coupling hole 32. In the table, a is the length of the major axis (mm), b is the length of the minor axis (mm), Table 1 is the axial ratio (dB) in circular polarization, and Table 2 is the major axis at that time.Length ofAnd short axisThe length ofRatio R (=b/a). In Tables 1 and 2, a region surrounded by a thick line indicates a part having an axial ratio of 3 dB or less. From this result, the long axisLength ofAnd short axisThe length ofRatio R (=b/a) Is preferably in the range of 0.86 to 0.97.
[0048]
[Table 1]

[0049]
[Table 2]

[0050]
  FigureIn the aperture antenna having the structure of FIGS. 1 to 3, one dielectric resonator 1 is mounted on the waveguide feed line 2. The dielectric resonator 1 is mounted at a predetermined interval, and each dielectric resonator 1 having an opening surface and the waveguide feed line 2 are coupled by the coupling hole 32 in the same manner as in FIGS. Thus, a series feed antenna can be formed.
[0051]
FIG. 6 is a perspective view showing an example of the series feeding antenna. In FIG. 6, the same parts as those shown in FIGS. 1 and 2 are denoted by the same reference numerals. In the figure, reference numeral 6 denotes a waveguide-type second feed line for feeding power to a plurality of two waveguide-type feed lines. Reference numeral 61 denotes the waveguide-type second feed line 6 and the waveguide-type feed line. 2 is formed at the end of the waveguide-type second feed line 6 (for convenience of explanation, half of the waveguide-type feed line 2 is omitted). Antenna port.
[0052]
In this figure, the high-frequency signal input from the antenna port 62 repeats branching, and is fed at the center in the longitudinal direction of the six waveguide feed lines 2 group in the slot 61 group. The high frequency signal coupled at the center in the longitudinal direction of the waveguide feed line 2 branches left and right, and five (10 in total on the left and right) dielectric resonators 1 arranged on the waveguide feed line 2. Join the group. Thereafter, linearly polarized light or circularly polarized light is radiated from the opening 31 of the dielectric resonator 1.
[0053]
In this case, it is necessary to adjust the coupling amount between each dielectric resonator 1 and the waveguide feed line 2 in order to control the radiation pattern. This adjustment can be appropriately adjusted by changing the size of the coupling hole 32, the diameter of the opening 31 at the top of the dielectric resonator 1, or the diameter d of the dielectric resonator 1.
[0054]
In addition, according to the present invention, by combining the waveguide feed line 2 and the dielectric resonator 1 with a conductor pattern and a vertical conductor in a multilayer wiring technique, on a dielectric substrate having a multilayer structure, A dielectric waveguide structure and a dielectric resonator structure can be formed, and the aperture antenna described above can be built in the multilayer wiring board.
[0055]
7 shows an example of a substrate with an aperture antenna (hereinafter simply referred to as an antenna substrate) in which the aperture antenna of FIG. 1 is formed in a dielectric substrate, where (a) is a plan view and (b) is a plan view. It is A1-B1 sectional view taken on the line of (a). In addition, the same code | symbol is attached | subjected to the part similar to what was shown in FIG. 1 thru | or FIG. In the antenna substrate of FIG. 7, a resonator unit dielectric substrate 51 is formed by laminating resonator unit dielectric layers 51 a and 51 b, and the resonator unit dielectric substrate 51 is led on the uppermost surface of the resonator unit dielectric substrate 51. The resonator layer lower main conductor layer 13 is formed on the lower surface of the body layer 11, and the resonator portion dielectric substrate 51 is sandwiched between the resonator portion main conductor layers 11 and 13.
[0056]
The upper main conductor layer 11 has an opening 31 where no conductor is formed. A plurality of resonator part through conductors 14 are provided around the opening 31 so as to electrically connect the resonator part upper main conductor layer 11 and the resonator part lower main conductor layer 13 with a predetermined interval. Is formed. The plurality of resonator portion through conductors 14 are arranged at a repetition interval of less than one half of the signal wavelength of the high frequency signal. Note that the repetition interval is not necessarily a constant value, and may be set by combining various values with less than half of the signal wavelength. Moreover, you may arrange | position with double and triple. An electromagnetic wave shielding body is formed by the plurality of through conductors 14 group, and this forms a pseudo conductor wall 1b of the dielectric resonator shown in FIG.
[0057]
The plurality of through conductors 14 are electrically connected between the upper main conductor layer 11 and the lower main conductor layer 13 by a resonator sub-conductor layer 12 provided in parallel with the main conductor layer. The resonator part sub-conductor layer 12 is provided with a conductor non-forming part similar in shape to the opening 31, and is formed as a single layer or a plurality of layers as necessary, together with a plurality of resonator part through conductors 14. A lattice-shaped resonator side conductor side wall 1 b is formed in the body substrate 51.
[0058]
  A resonator conductor comprising a resonator unit upper main conductor layer 11, a resonator unit lower main conductor layer 13, a plurality of resonator unit through conductors 14, and a resonator unit sub-conductor layer 12.At the wallThe dielectric resonator 1 structure is formed in the resonator part dielectric substrate 51 by the space surrounded and filled with the dielectric.
[0059]
  On the other hand, on the lower surface of the resonator unit dielectric substrate 51, a power feeding unit dielectric substrate 52 formed by laminating power feeding unit dielectric layers 52a and 52b is formed., SalaryThe power feeding unit upper main conductor layer 21 is formed on the upper surface of the power unit dielectric substrate 52, and the power feeding unit lower main conductor layer 23 is formed on the lower surface. The power feeding unit dielectric substrate 52 is composed of both power feeding unit main conductor layers. 21 and 23. In the figure, the resonator unit lower main conductor layer 13 and the power supply unit upper main conductor layer 21 areIntegratedIt is.
[0060]
Further, between the power feeding unit upper main conductor layer 21 and the power feeding unit lower main conductor layer 23, a plurality of power feeding unit penetrating conductors 24a and 24b are arranged in two rows so as to be electrically connected to each other. The plurality of through conductors 24a and 24b are arranged at a repetition interval of less than one half of the signal wavelength of the high frequency signal. Note that the repetition interval is not necessarily a constant value, and may be set by combining various values with less than half of the signal wavelength. Moreover, you may arrange | position with double and triple. The plurality of through conductors 24 a and 24 b are electrically connected between the upper main conductor layer 21 and the lower main conductor layer 23 by a power feeding portion sub-conductor layer 22 provided in parallel with the main conductor layer.
[0061]
An electromagnetic wave shielding body is formed by the plurality of through conductors 24a and 24b and the sub conductor layer 22, and this forms a pseudo E-plane conductor of the feeder line 2 in FIG.
[0062]
Then, it is surrounded by a pseudo conductor wall composed of a feed line portion upper main conductor layer 21, a feed line portion lower main conductor layer 23, a plurality of feed line portion through conductors 24a and 24b, and a sub conductor layer 22, and is filled with a dielectric. The formed space forms a feed line structure 2 made of a dielectric waveguide having a rectangular cross section.
[0063]
In particular, when this dielectric waveguide is used in a single mode, the interval w between the power feeding portion through conductor groups 24a and 24b is arranged such that λ / 2 <w <λ. The feeding portion dielectric layer 52 may be a single layer. In this case, the feeding portion sub-conductor layer 22 is not formed.
[0064]
  The resonator unit lower main conductor layer 13 (feeding unit upper main conductor layer 21) is formed with a nonconductor in order to couple the dielectric resonator structure 1 and the waveguide feed line structure 2. Forming partOvalCircleshapeThus, the dielectric resonator structure 1 and the waveguide feed line structure 2 are coupled to each other.
[0065]
And the electromagnetic wave of the high frequency signal radiated | emitted to the opening part 31 side through the coupling hole 32 from the waveguide type feed line 2 has a pair of main conductor layers 11 outside the space by having the dielectric resonator 1, The light is radiated from the opening 31 to the free space without propagating between the three.
[0066]
FIG. 8A shows an example of an antenna substrate in which an aperture antenna to which a reflection suppressing structure is added is formed in a dielectric substrate in the antenna substrate of FIG. 7, wherein FIG. 8A is a plan view, and FIG. ) Is a sectional view taken along line A2-B2 of FIG. The same parts as those shown in FIGS. 1 and 2 are denoted by the same reference numerals.
[0067]
In FIG. 8, a horizontal conductor 42 is provided by partially extending the feeder subconductor layer 22 inside the waveguide of the waveguide feedline structure 2, and the end of the horizontal conductor is a vertical conductor. 41 is electrically connected to the main conductor layer 23. In this way, the reflection suppressing structure 4 is formed in the waveguide feed line structure 2 from the reflection suppressing vertical conductor 41 and the reflection suppressing horizontal conductor 42.
[0068]
In the example of the embodiment of the present invention shown in FIG. 8, the reflection suppressing vertical conductor 41 is formed only on the power feeding portion dielectric layer 52b, but may be formed on the power feeding portion dielectric layer 52a. When the waveguide feed line 2 is formed of a number of dielectric layers, it may be formed on a plurality of layers.
[0069]
Note that, as described above, this antenna substrate functions as the antenna substrate that radiates linearly polarized waves shown in FIG. 4 and the antenna substrate that radiates circularly polarized waves shown in FIG. Can do. In addition, a series feed antenna substrate can be formed by arranging a plurality of dielectric resonator structures 1 at a predetermined interval with respect to the waveguide feed line structure 2.
[0070]
Further, according to the present invention, as shown in FIGS. 7 and 8, various circuits can be formed on other portions of the antenna substrate by forming the aperture antenna inside the dielectric substrate having a multilayer structure. Can do.
[0071]
FIG. 9 shows an example in which an active element is mounted on the back surface of the series-feed antenna substrate of the present invention, where (a) is a perspective view and (b) is a cross-sectional view along A3-B3 in (a). In the figure, 81 is a connection part for coupling the antenna port 62 and the surface circuit, 71 is a signal amplifier, 72 is a filter, 73 is a mixer, 74 is a high-frequency signal generator, and 82 is an IF port for IF signals.
[0072]
For example, the IF signal input from the IF port 82 is mixed with the carrier signal generated by the high-frequency signal generator 74 by the mixer 73, and after the high-frequency components such as out-of-band harmonics are cut by the filter 72, the signal amplifier Amplified at 71 and input to the antenna substrate via the connecting portion 81. Although it is not necessary that all the active elements 71 to 74 are mounted on the antenna substrate 5, at least the signal amplifier 71 is mounted on the antenna substrate 5 in the form of an antenna module, particularly when the signal wavelength uses a millimeter wave band. The merit is great in terms of transmission loss.
[0073]
10A and 10B show another example in which an active element is mounted on the back surface of the series-feed antenna substrate of the present invention. FIG. 10A is a perspective view, and FIG. 10B is a cross-sectional view taken along line A4-B4 in FIG. . The same parts as those shown in FIG. 9 are denoted by the same reference numerals. 75 is a signal switch such as a switch, circulator or diplexer, 82a is an IF input port, and 82b is an IF output port.
[0074]
The IF signal input from the IF input port 82a is mixed with the carrier signal generated by the high-frequency signal generator 74 by the mixer 73a, and after the high-frequency component such as out-of-band harmonics is cut by the filter 72a, the high-output signal is output. Amplified by the amplifier 71 a, a signal is sent only in the direction of the connection portion 81 by a signal switch 75 such as a switch, circulator, or diplexer, and is input to the antenna substrate 5. On the other hand, the signal received by the antenna substrate 5 and reaching the connection portion 81 is sent only to the low noise signal amplifier 71b by the signal switch 75, and after the signal outside the band is cut by the filter 72b, The signal generated by the signal generator 74 is mixed with the mixer 73b, and only the IF signal is extracted. Thereafter, the data is output from the IF output port 82b. Thus, by providing the signal switching device 75, it is possible to provide an antenna substrate for both transmission and reception.
[0075]
FIGS. 11A and 11B show an example of a configuration in which a semiconductor element is mounted in the cavity on the back surface of the antenna substrate of the series feed of the present invention, where FIG. 11A is a perspective view and FIG. 11B is A5-B5 in FIG. It is sectional drawing. The same parts as those shown in FIG. 10 are denoted by the same reference numerals. 7 is a semiconductor element, and 9 is a cavity.
[0076]
The semiconductor element 7 may have a single function such as a switch or a signal amplifier, or may be an integrated group of functional elements shown in FIG. 9 or FIG.
[0077]
Thus, by forming the cavity 9 on the back surface of the antenna substrate 5, the semiconductor element 7 can be accommodated in the cavity 9, so that the antenna substrate 5 having high characteristics and low cost can be realized.
[0078]
The dielectric substrate in the above antenna substrate can be easily formed by laminating a dielectric layer having an appropriate thickness. The conductor layer can be formed by printing a conductor paste or conductor foil, and the vertical conductor can be easily formed by forming a through hole in the dielectric layer and filling the conductor paste by screen printing or the like. it can. In particular, since a low-resistance conductor such as copper, silver, or gold is used as the dielectric material, the dielectric substrate is a known low-temperature fired ceramic material that can be fired at 1050 ° C. or lower, such as borosilicate glass, or Borosilicate glass and SiO₂, Al₂O_ThreeFor example, the transmission loss is reduced and the antenna characteristics are improved.
[0079]
【Example】
Next, a specific example of the aperture antenna of the present invention will be described.
FIG. 12 is a diagram illustrating the effect of the reflection suppression structure of the antenna substrate having the reflection suppression structure of FIG. The dielectric substrates 51 and 52 of FIG. 8 are made of glass ceramics having a relative dielectric constant of 4.9, the thickness of the dielectric resonator 1 is 0.6 mm, and the size of the waveguide feed line 2 is (w, h ) = (1.82 mm, 0.6 mm), and the center position of the coupling hole 32 is set to a shift amount c = 0.39 mm from the central axis of the waveguide feed line 2. The frequency was evaluated at 62.5 GHz.
[0080]
FIG. 12A shows the reflection characteristics when the coupling hole 32 has an elliptical shape and its size a (the major axis and minor axis of the ellipse are b = 1.44a−0.52) is changed. The diameter of the dielectric resonator d and the opening size were 2.12 mm.
[0081]
As the reflection suppressing structure, a horizontal conductor 42 having a width of 0.2 mm and a length of 0.67 mm is provided below the coupling hole 32 in FIG. 8 at the position of a thickness of 0.3 mm of the waveguide feed line. 22, a structure in which a vertical conductor 41 having a diameter of 0.2 mm extends to the lower main conductor layer (E-plane conductor) 23 at the end of the horizontal conductor 42 inside the waveguide feed line 2. It was formed symmetrically.
[0082]
In the figure, ● represents the result when the reflection suppressing structure 4 is added, and Δ represents the result when the reflection suppressing structure 4 is not provided. In the case where there is no reflection suppressing structure 4, the reflection is larger than −20 dB, whereas in the case where there is the reflection suppressing structure 4, it is understood that the reflection is suppressed to −30 dB or less.
[0083]
FIG. 12B is a diagram illustrating the reflection characteristics when the diameter d of the dielectric resonator 1 is changed. The size of the elliptical coupling hole 32 was set to a = 1.000 mm, b = 0.914 mm, and the reflection suppressing structure 4 was the same as that in FIG. The size of the opening 31 is the same as the diameter d of the dielectric resonator 1. In the figure, ● represents the result when the reflection suppressing structure 4 is added, and Δ represents the result when the reflection suppressing structure 4 is not provided. In the case where there is no reflection suppressing structure 4, the reflection is larger than −20 dB, whereas in the case where there is the reflection suppressing structure 4, it is understood that the reflection is suppressed to −30 dB or less.
[0084]
  FIG.OpenUse a mouth antenna to radiate circular or linearly polarized waves.ExampleIt is the radiation pattern of the antenna which shows. In the figure, the horizontal axis represents the angle from the normal direction of the antenna surface, and the vertical axis represents the relative intensity of the electromagnetic wave. A solid line indicates a right-handed circularly polarized wave component, and a broken line indicates a left-handed circularly polarized wave component. The evaluation was performed at 62.5 GHz.
[0085]
The dielectric layer is made of glass ceramics having a relative dielectric constant of 4.9, the diameter d of the dielectric resonator 1 and the size of the opening 31 are φ2.12 mm, the thickness of the dielectric resonator 1 is 0.6 mm, and an ellipse. The size of the shape coupling hole 32 was a = 1.000 mm, b = 0.914 mm, and the size of the waveguide feed line 2 was (w, h) = (1.82 mm, 0.6 mm). Further, a reflection suppressing structure having the same structure as that formed in FIG. 12 was formed.
[0086]
  FIG. 13 (a)IsThe deviation c from the central axis of the waveguide feed line 2 at the center position of the elliptical coupling hole 32 is set to c = 0.39 mm.It is a graph which shows the result of the aperture surface antenna of this invention.. In this case, the left-handed circularly polarized wave component in the normal direction (0 ° direction) is −30 dB or less, and most is the right-handed circularly polarized wave component. That is, it can be seen that clean right-handed circularly polarized electromagnetic waves are radiated.
[0087]
  FIG. 13 (b)IsThe center position of the elliptical coupling hole 32 is the center of the waveguide feed line 2.Is a graph showing the results of. In this case, the right-handed circularly polarized wave component of the solid line and the left-handed circularly polarized wave component of the broken line coincide with each other. That is, it can be seen that clean linearly polarized electromagnetic waves are radiated.
[0088]
FIG. 14A is a diagram showing the relationship between the coupling hole size, the radiation amount, and the axial ratio of the circularly polarized wave, and FIG. 14B is a diagram showing the change of the axial ratio with respect to the frequency.
[0089]
The dielectric substrates 51 and 52 are made of a material having a relative dielectric constant of 4.9, the thickness t of the dielectric resonator 1 is 0.6 mm, the diameter d of the dielectric resonator 1 and the size of the opening 31 are 2.12 mm. The size of the waveguide feed line 2 is (w, h) = (1.82 mm, 0.6 mm). The deviation c from the central axis of the waveguide feed line 2 at the center position of the elliptical coupling hole 32 was set to c = 0.39 mm. Further, a reflection suppressing structure having the same structure as that formed in FIG. 12 was formed.
[0090]
FIG. 14A shows the relationship between the amount of radiation and the axial ratio when the elliptical coupling hole 32 size a (the major axis of the ellipse and the minor axis are b = 1.44a−0.52) is changed. It is a figure and the frequency is evaluated at 62.5 GHz.
[0091]
In the figure, ● represents the amount of radiation, and □ represents the axial ratio in circular polarization. From this figure, by changing the elliptical coupling hole size from 0.86 mm to 1.02 mm, the radiation amount can be controlled to 10 to 60%, and the axial ratio at that time also has good characteristics within 3 dB. I understand that
[0092]
FIG. 14B is a diagram showing the frequency dependence of the axial ratio when the size of the elliptical coupling hole 32 is a = 1.020 mm. From this figure, it can be seen that even if the frequency is changed from 55 to 65 GHz and 10 GHz, the change of the axial ratio is small at about 1 dB or less.
This means that the change in the axial ratio is very small even if the dimensional accuracy changes.
[0093]
FIG. 15A is a diagram showing the relationship between the size of the opening 31 and the radiation amount and the axial ratio of the circularly polarized wave, and FIG. 15B shows the diameter d of the dielectric resonator 1, the radiation amount, and the circular polarization. It is a figure which shows the relationship of the axial ratio of a wave.
[0094]
The dielectric substrates 51 and 52 are made of glass ceramics having a relative dielectric constant of 4.9, the thickness t of the dielectric resonator 1 is 0.6 mm, and the size of the waveguide feed line 2 is (w, h) = (1.82 mm, 0.6 mm). The deviation c from the central axis of the waveguide feed line 2 at the center position of the elliptical coupling hole 32 was set to c = 0.39 mm. Further, a reflection suppressing structure having the same structure as that formed in FIG. 12 was formed.
[0095]
FIG. 15A is a diagram showing the relationship between the radiation amount and the axial ratio when the size d of the opening 31 is changed, and the frequency is evaluated at 62.5 GHz. The diameter of the dielectric resonator 1 is constant at 2.12 mm. In the figure, ● represents the amount of radiation, and □ represents the axial ratio in circular polarization. From this figure, by changing the opening size from 1.5 mm to 2.2 mm, the amount of radiation can be controlled to 10 to 60%, and good characteristics with an axial ratio within about 2 dB can be obtained. I understand that.
[0096]
FIG. 15B is a diagram showing the relationship between the radiation amount and the axial ratio when the diameter of the dielectric resonator 1 is changed, and the frequency is evaluated at 62.5 GHz. Note that the size of the opening 31 is the same as the diameter of the dielectric resonator 1. In the figure, ● represents the amount of radiation, and □ represents the axial ratio in circular polarization. From this figure, by changing the resonator diameter from 1.5 mm to 2.2 mm, the radiation amount can be controlled to 2 to 60%, and the axial ratio at that time also has good characteristics within about 1.5 dB. It turns out that it is obtained.
[0097]
FIG. 16 is a diagram showing an example of radiation pattern control by the series feeding method shown in FIG. In this case (see FIG. 6), the series-fed waveguide feed line 2 is fed at the center by the slot 61, and after branching, the radiation amounts of the five dielectric resonators 1 arranged on the left and right are symmetrical. At this time, the amount of radiation from the dielectric resonator 1 from the center toward the end is changed to 42%, 52%, 58%, 60%, 62 by changing the coupling hole size, the opening size, and the resonator size as described above. %. The antenna element spacing is the free space wavelength λ₀, 5.25λ₀It was. As shown in FIG. 16, in this case, it can be seen that the side lobe level is controlled to -25 dB or less.
[0098]
【The invention's effect】
  As detailed above, according to the aperture antenna of the present invention,OvalRoundConditionSince the resonance frequency can be controlled by the coupling hole and the dielectric resonator, even if there is an error of several percent in the dimensional accuracy of the coupling hole, the resonance in the desired frequency band can be stably obtained. The electromagnetic wave of the high frequency signal radiated from the opening surface can be radiated stably. In addition, since there is no unnecessary radiation on the feeder line and the transmission loss is small, the loss at the antenna can be reduced, and the elliptical typeConditionBy adjusting the positional relationship between the coupling hole and the dielectric waveguideTheA right-handed circularly polarized wave and a left-handed circularly polarized wave can be emitted.
[0099]
Further, by forming a structure for suppressing reflection in the waveguide or dielectric waveguide located below the coupling hole in the waveguide or dielectric waveguide, the impedance shift at the antenna element coupling portion The reflected wave due to can be sufficiently suppressed. Furthermore, since the reflected wave can be sufficiently suppressed even in the case of series feeding, the reflection loss can be reduced even if the antenna element is set to approximately one in-tube wavelength interval of the dielectric waveguide and the radiation beam is set in the normal direction of the antenna surface. It can be suppressed.
[0100]
  Furthermore, the elliptical coupling hole of the laminated aperture antenna, the circular shape of the dielectric resonatorIn shapeSince the amount of radiation is adjusted by changing the size of the aperture and the diameter of the dielectric resonator, the radiation pattern can be easily controlled, and the axial ratio can be reduced even in the case of circular polarization.SuppressionIt will be something that can be obtained.
[0101]
Furthermore, a dielectric waveguide capable of transmitting a high-frequency signal in the dielectric substrate, and an opening for radiating the high-frequency signal to space, all or part of the side surface of the cylindrical dielectric is covered with metal. And a coupling hole is formed at a position facing the center of the opening of the cylindrical dielectric resonator in the H-plane conductor of the dielectric waveguide. A high-frequency signal is fed from the dielectric waveguide to the cylindrical dielectric resonator through the hole, so that an active element or a signal switch is directly mounted on the back surface of the dielectric substrate or a cavity is formed. However, it can be incorporated in the antenna substrate, and it can be a small, highly reliable, low-cost antenna substrate.
[Brief description of the drawings]
FIG. 1 is a schematic perspective view showing an example of an aperture antenna according to the present invention.
[Figure 2](A)An example of the aperture antenna having the reflection suppressing structure of the present invention is shown.OutlineSchematic perspective viewAnd, (B)IsIt is xx sectional drawing of (a).
[Fig. 3]OpenIt is a figure which shows the example of the shape of the coupling hole of a surface antenna.
[Fig. 4](A) is straightAn example of a laminated aperture antenna that radiates linearly polarized wavesSuhiraAreaAnd, (B)IsIt is a figure which shows magnetic field distribution.
[Figure 5](A)An example of a laminated aperture antenna that radiates circularly polarized waves in the present invention is shown.SuhiraAreaAnd, (B)IsIt is a figure which shows magnetic field distribution.
FIG. 6 is an exploded view showing an example of a series feed antenna using the aperture antenna of the present invention.
[Fig. 7](A)An example of the board | substrate with an aperture antenna of this invention is shown.SuhiraAreaAnd, (B)IsIt is A1-B1 sectional drawing of (a).
[Fig. 8](A)An example of the board | substrate with an aperture surface antenna which has the reflection suppression structure of this invention is shown.SuhiraAreaAnd, (B)IsIt is A2-B2 sectional drawing of (a).
FIG. 9(A)An example in which an active element group is mounted on a substrate with an aperture antenna of the present invention is shown.SlantViewAnd, (B)IsIt is A3-B3 sectional drawing of (a).
FIG. 10(A)An example in which an active element group is mounted on a substrate with an aperture antenna of the present invention and used for both transmission and reception is shown.SlantViewAnd, (B)IsIt is A4-B4 sectional drawing of (a).
FIG. 11(A)An example in which a cavity is formed in a substrate with an aperture antenna of the present invention is shown.SlantViewAnd, (B)IsIt is A5-B5 sectional drawing of (a).
12A and 12B are diagrams showing the effect of the reflection suppressing structure in the aperture antenna of the present invention, where FIG. 12A is a characteristic when the coupling hole size is changed, and FIG. 12B is a graph when the resonator diameter is changed. It is a characteristic.
FIG. 13(A)Aperture antenna of the present inventionFromRadiation pattern indicating that the radiated electromagnetic wave is circularly polarizedAnd, (B), the radiated electromagnetic wave is linearly polarizedsituationalIt is a figure which shows a radiation pattern.
FIG. 14(A)In the aperture antenna of the present inventionRuAperture size, radiation, and axial ratio of circular polarizationWhen(B) is a figure which shows the change of the axial ratio with respect to a frequency.
FIG. 15(A)The aperture antenna of the present inventionKickAperture size, radiation, and axial ratio of circular polarizationWhen(B) is a diagram showing the relationship between the resonator diameter, the radiation amount, and the axial ratio of circularly polarized waves.
FIG. 16 shows an aperture antenna according to the present invention.,It is a figure which shows an example of the radiation pattern control by a serial feeding system.
[Explanation of symbols]
1 Dielectric resonator
11 Resonator upper main conductor layer
12 Resonator section sub-conductor layer
13 Lower main conductor layer of resonator part
14 Resonator part through conductor
2 Waveguide feed line
21 Upper main conductor layer of the power feeding unit
22 Feeder sub-conductor layer
23 Lower main conductor layer of the feeding section
24 Feeder penetration conductor
31 opening
32 coupling hole
4 reflection suppression structure
41 Anti-reflection vertical conductor
42 Antireflection horizontal conductor
5 PCB with antenna
51 Dielectric substrate for resonator part
52 Dielectric substrate for feeding section

Claims (17)

All or part of the side surface of the cylindrical dielectric is constituted is covered with an electromagnetic wave shield, and a cylindrical dielectric resonator having an opening for radiating a high-frequency signal into space whereas the main surface, the comprising a cylindrical waveguide for feeding the dielectric resonator or dielectric waveguide, the other of said cylindrical dielectric resonators H plane conductor surface of the waveguide or dielectric waveguide Rutotomoni have main surface is attached to the center and the opposite position of the opening of the cylindrical dielectric resonator in the H plane conductor of the waveguide or dielectric waveguide, the waveguide or binding holes of an oval shape centered at a position deviated from the center axis of the dielectric waveguide is formed, the cylindrical high-frequency signal from the waveguide or dielectric waveguide through said coupling hole aperture antenna, wherein Rukoto powered in the dielectric resonator. When said free air Maha length of the dielectric material of the high-frequency signal is a lambda, the opening according to claim 1, wherein the thickness of said cylindrical dielectric resonator characterized in that it is a λ / 4~λ / 2 Planar antenna. The waveguide or in the dielectric waveguide located below the coupling hole, according to any one of claims 1 to 2, characterized that you have suppressing structure reflected is formed Aperture antenna. When the width of the waveguide or dielectric waveguide is w, the center of the coupling hole is at a position shifted from w / 8 to 3w / 8 from the central axis of the waveguide or dielectric waveguide. The aperture antenna according to any one of claims 1 to 3, wherein: When the ratio of the length of the major axis length and minor axis of the coupling hole of the elliptical shape and the R (= the length of the length / long axis of the minor axis), R is at 0.86 to 0.97 The aperture antenna according to any one of claims 1 to 3, wherein the aperture antenna is provided. The H plane conductor surface of the waveguide or dielectric waveguide, a plurality of said cylindrical dielectric resonators are mounted generally with 1 guide wavelength spacing, by the waveguide or dielectric waveguide all aperture antenna according to any one of claims 1 to 5 wherein the series feed into a cylindrical dielectric resonator, characterized in Rukoto. Radiation amount is adjusted by changing the size of the coupling hole in the plurality of series feed is columnar dielectric resonator, opening in claim 6, wherein the total radiation pattern is characterized Rukoto controlled Planar antenna. Radiation amount is adjusted by changing the size of the opening of the plurality of series feed is columnar dielectric resonator, opening in claim 6, wherein the total radiation pattern is characterized Rukoto controlled Planar antenna. Is adjusted radiation amount by changing the size of the diameter of said plurality of series feed is columnar dielectric resonator, aperture antenna according to claim 6, wherein Rukoto overall radiation pattern is controlled . A plurality of dielectric layers are laminated dielectric substrate, and a dielectric waveguide structure capable of transmitting high-frequency signals, all or a portion of the side surface of the cylindrical dielectric is covered by an electromagnetic wave shielding wall structure are, the high-frequency signal; and a cylindrical dielectric resonator structure having a first major surface an opening for radiating to a space, the over H plane conductors of said dielectric waveguide structure will place the cylindrical dielectric resonator structure as the other main surface is bonded, the opening of the cylindrical dielectric resonator structure in the H plane conductors of said dielectric waveguide structure the faces the center of the coupling hole of the elliptical shape centered at a position deviated from the center axis of the dielectric waveguide structure is formed, the high frequency signal is the dielectric through the coupling hole JP the Rukoto powered on the cylindrical dielectric resonator structure from the Karadashirubeha tube structure Aperture antenna with a substrate to be. More the dielectric waveguide structure, to be electrically connected to the feeding portion upper main conductor layer and the power feeding portion lower main conductor layers, the feeding portion upper main conductor layer and the power supply unit lower main conductor layer at predetermined intervals aperture antenna with a substrate according to claim 10, wherein Rukoto includes an electromagnetic wave shielding wall consisting of a feeding unit through conductors. The plurality of through conductors, wherein between the feeding portion upper main conductor layer and the power feeding portion lower main conductor layers, the feeding portion upper main conductor layer and the power feeding subordinate unit main conductor layer and the power feeding part provided in parallel aperture antenna with a substrate according to claim 11, wherein that you have been electrically connected by the sub-conductor layers. Said cylindrical dielectric resonator structure, the a resonator portion upper main conductor layer having the opening formed on the surface of the dielectric substrate, formed resonators lower at a position opposed to the opening a main conductor layer, wherein formed in the dielectric substrate around the opening, a plurality of resonance which electrically connects the resonator portion lower main conductor layer and the cavity portion upper main conductor layer at predetermined intervals a vessel section through conductor, between said cavity portion upper main conductor layer and the cavity portion lower main conductor layers, provided parallel to said resonator section upper main conductor layer and the resonator subordinate unit main conductor layer and said plurality of resonators aperture antenna according to any one of claims 10 to 12, characterized in Rukoto an antenna conductor wall composed of a resonator portion sub-conductor layers through the conductor electrically connecting With board. Wherein the back surface of the dielectric substrate, at least one aperture antenna with a substrate according to any one of claims 10 to 13 signal amplifier characterized that you have been implemented. Wherein the back surface of the dielectric substrate, switches, circulator and diplexer aperture antenna with a substrate according to any one of claims 10 to 14, at least one selected from the group is characterized that you have been implemented in. Wherein the back surface of the dielectric substrate, aperture antenna with a substrate according to any one of claims 10 to 15, characterized in Rukoto cavity is formed for accommodating a semiconductor element. Aperture antenna with a substrate according to any one of claims 10 to 16 made of the dielectric substrate is characterized by low temperature co-fired ceramic der Rukoto.

Images