CN1322408A - Transmission over bundled channels in CDMA mobile radio system - Google Patents

Transmission over bundled channels in CDMA mobile radio system Download PDF

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Publication number
CN1322408A
CN1322408A CN00801845A CN00801845A CN1322408A CN 1322408 A CN1322408 A CN 1322408A CN 00801845 A CN00801845 A CN 00801845A CN 00801845 A CN00801845 A CN 00801845A CN 1322408 A CN1322408 A CN 1322408A
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channel
signal
spread spectrum
spectrum signal
combination
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Chinese (zh)
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X·B·李
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Koninklijke Philips NV
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Koninklijke Philips Electronics NV
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/14—Relay systems
    • H04B7/15—Active relay systems
    • H04B7/204—Multiple access
    • H04B7/216—Code division or spread-spectrum multiple access [CDMA, SSMA]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B2201/00—Indexing scheme relating to details of transmission systems not covered by a single group of H04B3/00 - H04B13/00
    • H04B2201/69—Orthogonal indexing scheme relating to spread spectrum techniques in general
    • H04B2201/707—Orthogonal indexing scheme relating to spread spectrum techniques in general relating to direct sequence modulation
    • H04B2201/70706—Orthogonal indexing scheme relating to spread spectrum techniques in general relating to direct sequence modulation with means for reducing the peak-to-average power ratio

Abstract

A transmitter apparatus and transmitting method are provided for implementing a high data rate multi-channel link in a digital Code Division Multiple Access (CDMA) wireless communications system composed of three or more individual lower data rate traffic channels represented in a transmitted combined RF signal, which are distributed over a set of phase offsets of a sinusoid carrier in the range of 0 to pi radians, in which a combined complex spread spectrum signal, composed of an in-phase component and a quadrature-phase component, is formed prior to up-conversion in a manner that all the required phase offsets of the represented channels are introduced. The three or more individual lower data rate channels include two or more individual channels having phase offsets which are 0, pi /2, or pi radians, and one or more individual channels having phase offsets which are pi /4 or 3 pi /4 radians. Individual complex spread spectrum signals are formed for the respective individual channels, each composed of an in-phase component and a quadrature-phase component. Further complex spread spectrum signals are derived therefrom (or merely repeated) for the individual channels in a manner including the introduction of fractional scaling factors having an absolute value substantially equal to [square root of] 2ROOT 2/2 for the channels having phase offsets of (/4 or 3(/4 radians, and these derived signals are additively combined to form the complex combined spread spectrum signal.

Description

In the bundled channels of CDMA mobile radio system, transmit
Background of invention
TECHNICAL FIELD OF THE INVENTION
The present invention relates to be used for transmit the data of same communication so that data rate that obtains to be equivalent to provide for this communication or many times apparatus and method of bandwidth by single Traffic Channel in a plurality of of communication system or cluster Traffic Channel.Unique aspect of the present invention is, it relates to the transmitter architecture of multi-channel reverse link in digital code division multiple access (CDMA) wireless communication system, wherein each individual channel of expressing in the combination RF signal that is sent out is distributed in the scope of one group of phase-shift value, so that reduce the peak-to-average ratio of RF signal in this group phase-shift value scope of this combination, if the carrier phase of the channel that these are independent is to aim to arrange, this just can accomplish.
Description of Related Art
A kind of system like this can with people such as high pass (Qualcomm) E.Tiedemann of limited company in the meeting of holding in Philadelphia 16-20 day in June, 1997, submit to the TR45.5 committee of telecommunications industry association (TIA) the system that is entitled as " improving reverse link peak-to-average ratio (phase place 1c) ", learn from the interim standard I S-95B of TIA/EIA and from PCT patent application WO98/58457.
In 1992, direct sequence code division multiple access (DS-CDMA) system was together adopted as the interim standard I S-95 that is used for the cellular band of 800MHz by TIA and Electronic Industries Association (EIA).After successfully carrying out field test and experimental system, now, the IS-95 system can carry out work for tens million of users.CDMA is based on the spread spectrum that proposed at first by Allies for the radio interference of resisting the enemy in the World War II.The feature of spread-spectrum signal is that its signal occupied bandwidth W is much larger than information rate R bps of signal.Like this, spread-spectrum signal comprises a kind of various interference redundant information of (comprising signal and because the self-interference that the multipath composition of time delay causes from same other user of wave band) that can be used for overcoming inherently.Another key characteristic of spread-spectrum signal is a pseudo-randomness.Therefore, this signal shows and is similar to random noise, and this makes the receiver except predefined receiver be difficult to it is carried out demodulation.In cdma system, each Channel Sharing common bandwidth is distinguished channel by different sign indicating number sequences.Under the situation of IS-95, one of each channel bearing is known as the signal of information encoded (this walsh code is assigned to this channel (be known as use Walsh cover)) of a particular sequence modulation in the orthogonal sequence group of Walsh (Walsh) sign indicating number, again by modulation of long pseudo noise (PN) sign indicating number or upset, for directly carry out by these in-phase components and quadrature phase component respectively with the up-conversion that homophase is sinusoidal wave and the quadrature phase sine wave multiplies each other of carrier frequency, process in-phase modulation and quadrature phase PN short code are modulated homophase (I) and quadrature phase (Q) the spread-spectrum signal component to form complex spread spectrum signal respectively again, homophase and quadrature phase are formed the RF signal in multiplied result summation back separately, deliver to then and offer antenna again after the RF power amplifier amplifies.
In nineteen ninety-five, IS-95 is expanded to interim standard I S-95A, becomes interim standard I S-95B thereafter again.Back one expansion provides high band wide data to use, and can use nearly 8 one group or cluster channel to transmit data in same communication, hangs down data rate channel from this group effectively and has formed a high data rate channel.
The IS-95B regulation, when a plurality of channels are used for forming a multichannel chain-line, if the homophase of each channel carrier wave frequency sine wave and quadrature phase sine wave are to there being 0 phase shift, in order to reduce the peak-Ping power that makes up the RF signal in this case, then this sine wave of the carrier frequency of these channels is 0 between the π radian to be dispensed on phase shift range with specific sub-optimal manner in reverse link (transmission from the mobile radio station to the base station).The distribution of this phase shift has reduced the linearity and the dynamic range requirement of transmitting power of mobile station amplifier.Especially, the phase shift that is applied to the homophase of up-convert channel 0-3 and channel 4-7 and quadrature phase sine wave be respectively 0, pi/2, π/4 and 3 π/4 radians.
As everyone knows, be the analog signal that produces by oscillator at the homophase of carrier frequency and quadrature phase sine wave, this analog signal and simulated by the analog signal that the homophase and the quadrature phase spread spectrum digital signal components of channel converts to multiplies each other.Homophase and quadrature phase spread-spectrum signal component for each channel that reaches 8 channels use independent D/A converter, or suppose the D/A conversion that provides independent, have consequently increased the complexity and the cost of mobile radio station.In addition, when homophase and quadrature phase sine wave are oscillator sections by mobile radio station when producing, the sine wave that stably produces π/4 and 3 π/4 phase shifts is problematic.
Foregoing PCT patent application shows, in this patent application, have only two channels to be used for making up, form the homophase spread-spectrum signal component of combination and, may introduce the pi/2 phase shift of second channel by back addition that the quadrature phase spread-spectrum signal component of the homophase spread-spectrum signal component of first channel and second channel is negated the quadrature phase component of the homophase spread-spectrum signal component addition formation combination of the quadrature phase spread-spectrum signal component of first channel and second channel.Then, the homophase of combination and quadrature phase component directly multiply each other with the homophase of carrier frequency and quadrature phase sine wave respectively and carry out up-conversion, and these product terms are formed the RF signal that makes up mutually.Yet, when three or more channels is used to make up, certainly will causes π/4 phase shifts, and also may be 3 π/4 phase shifts, this just requires to adopt one group of homophase and quadrature phase sine wave, and it comprises having π/homophase and the quadrature phase sine wave of 4 phase shifts at least.
Goal of the invention and summary
The objective of the invention is provides one type multichannel chain-line structure in digital code division multiple access (CDMA) wireless communication system, in this type, the a plurality of different Traffic Channel of in the combination RF signal that sends, representing be distributed on phase shift range be 0 and the π radian between one group of sinusoidal carrier on, this only needs the combination homophase spread-spectrum signal component of a combination complex spread spectrum signal and combination quadrature phase spread-spectrum signal component are carried out the D/A conversion, and for the paired signal of deriving by combination homophase and combination quadrature phase spread-spectrum signal component in unlike signal multiply each other, only need on carrier frequency, to produce a pair of homophase and quadrature phase sine wave.In the mobile radio station of the multichannel chain-line that this capable use is made up of three or more individual channels, such structure will obtain simplifying, and reduce the cost of base band and RF part.
This and other purpose of the present invention satisfied with providing a kind of like this transmitter installation and sending method to realize, the phase shift of all requirements in this transmitter installation and sending method (comprise that two or more phase shifts are 0, the phase shift of the independent channel that is expressed of pi/2 or π and one or more phase shifts are not 0, the phase shift of the independent channel that is expressed of pi/2 or π radian) is introduced into when the quadrature phase spread-spectrum signal component of homophase that generates combination and combination.In order to realize this scheme, at first will form each different complex spread spectrum signal (its each all form) of each corresponding individual channel, and the signal that the combination of addition ground is derived by each different complex spread spectrum signal of each individual channel is so that forms the complex spread spectrum signal that makes up by in-phase component and quadrature phase component.The combination of this addition ground is such: from the signal that one or more phase shifts are not 0, each complex spread spectrum signal of the channel of pi/2 and π radian is derived, be to come the signal that is 0, each complex spread spectrum signal of the channel of pi/2 and π is derived converted and obtain by using relevant fractional scaling factor from two or more phase shifts.More particularly, those are not 0, the phase-shift value of pi/2 or π is exactly π/4 or 3 π/4, and described fractional scaling factor has absolute value
In addition, the device that the device of addition ground combination maybe can play this effect be arranged to can so that the homophase of combination spread-spectrum signal and quadrature phase component receive respectively from phase shift be 0, part in the signal of deriving in the homophase of each complex spread spectrum signal of the channel of pi/2 or π or any rather than whole two signals the quadrature phase component, simultaneously, their receive from phase shift be not 0, the part of the signal of deriving the homophase of each complex spread spectrum signal of the channel of pi/2 or π and quadrature phase component whole two.According to the first embodiment of the present invention, the homophase of each complex spread spectrum signal of each different channels and quadrature phase component be sent to respectively separately finite impulse response (FIR) (FIR) filter or the input of filtering operation, its output or result deliver to the device that the device that is used for addition ground combination maybe can play this effect.
Second embodiment according to the present invention, the homophase of each complex spread spectrum signal of each individual channel and quadrature phase component be sent to respectively separately finite impulse response (FIR) (FIR) filter or the input of filtering operation, its output or result deliver to the device that the device that is used for addition ground combination maybe can play this effect.The advantage of this embodiment is only to need two filters or filtering operation, rather than every individual channel all needs two.
By studying following detailed carefully simultaneously with reference to accompanying drawing, other purpose of the present invention, characteristics and advantage will be clearly, wherein:
The accompanying drawing summary
Fig. 1 is applied in the mobile radio station in the Digital Cellular System (as cdma system) or the general schematic of hand-held set; And
Fig. 2 and Fig. 3 are respectively the functional schematics according to mobile radio station transmitter embodiment part shown in Figure 1 in first and second embodiment of the present invention.
DESCRIPTION OF THE PREFERRED
At first with reference to accompanying drawing 1, the mobile radio station transceiver 10 of traditional Digital Cellular System (as cdma system) of detailed description comprises a user interface section 12 that is connected to Base Band Unit 14 (it is connected to radio frequency unit 16 again).User interface section 12 also is connected to keyboard 18, LCD demonstration 20, microphone 22 and loud speaker 24.Base Band Unit 14 comprises a digital signal processor (DSP) 26, its addressable random access memory and the read-only memory 30 that comprises firmware instructions.Base Band Unit 14 also comprises a clock 32, one and is used in particular for receiving the digital to analog converter (A/D ' s) 34 that 34 and one of analog to digital converters from the analog signal of the RF unit 16 in forward direction (receptions) link (A/D ' s) are used in particular for providing analog signal to the RF unit 16 in reverse (transmission) link.
RF unit 16 comprises an oscillator 38, and it is used for producing the sine wave of carrier frequency, and it is offered the zero IF frequency downconverter 40 of forward link and the zero IF frequency up-converter 42 of reverse link.Antenna 48 is delivered to input amplifier 44 through antenna diplexer 46 with signal, the RF signal that low-converter 40 receives from input amplifier 44, on the contrary upconverter 42 offers output or power amplifier 50 with the RF signal, delivers to antenna 48 through antenna diplexer 46 again.
As what will in the description of first and second embodiments of the present invention, manifest very soon, in order to form the multi-channel reverse link formed by three or more channels and all carrier phase of needs be achieved in that and in the DSP 32 of Base Band Unit 14, handle, upconverter 42 in the startup RF unit 16 is used for the homophase of multiple composite signal and the homophase and the quadrature phase sine wave of quadrature phase component and carrier frequency are multiplied each other with frequency mixer or the multiplier of partnering.
Forward the Fig. 2 about first embodiment to, it has shown the parts 52 that baseband portion 14 realizes, it receives the data-signal DS of N the channel that forms multi-channel reverse link respectively 0-DS N, and form a kind of by analog combined spread spectrum in-phase component ACSS IWith analog combined spread spectrum quadrate-phase component ACSS QThe analog complex combined spread spectrum signal of forming.Reach 8 channels though in IS-95B, form the channel of multichannel chain-line, only demonstrate 4 channels to be convenient to graphic extension.The Base-Band Processing scheme of channel 0-3 is the same with channel 4-7, and this is because the phase shift sequence of the homophase that is used for up-convert channel 0-3 that provides of IS-95B and quadrature phase sine wave is the same with what be used for channel 4-7, promptly 0, pi/2, π/4,3 π/4 radians.Obviously, these additional channels only are to add more part to this to simulation combination spread-spectrum signal component A CSS IAnd ACSS QIn.Above-mentioned these components are fed in the zero IF up-converter of realizing in the RF unit 16 54.In upconverter 54, simulation combination homophase and quadrature phase spread-spectrum signal component A CSS IAnd ACSS QOffer low pass filter 140 and 141 respectively, their output is as the homophase and the sinusoidal wave sin (w of quadrature phase of carrier frequency cT) and cos (w cT) be sent to respectively in frequency mixer or multiplier 144 and 146.The output of frequency mixer or multiplier 144 and 146 is delivered in the adder 150 to form the combination RF signal CRF that will offer power amplifier 150.
Base-Band Processing parts 52 comprise parts 58 and parts 56.Parts 58 are in a conventional manner according to each input data signal DS 0To DS 3Form each different homophase and quadrature phase spread spectrum digital signal components respectively to DSS 0I, DSS 0QTo DSS 3I, DSS 3QParts 56 filtering, conversion and make up each different homophase and quadrature phase spread spectrum digital signal components to DISS 0I, DISS 0QTo DISS 3I, DISS 3Q, to form combination of numbers homophase and quadrature phase spread-spectrum signal component to DCSS IAnd DCSS Q, in this processing procedure, introduce or considered the influence of the desired carrier phase of each channel.Combination of numbers component DCSS IAnd DCSS QBe provided to digital to analog converter 140 and 142 respectively so that form simulation combination component A CSS IAnd ACSS Q
In parts 58, each input data signal DS 0, DS 1, DS 2And DS 3Be provided to channel encoder 61,71,81 and 91 separately respectively, and the encoded data signals of carrying out frame by frame that obtains is at last delivered to respectively in separately the Walsh modulator 62,72,82 and 92, so that use the walsh code of each channel special use that encoded data signals is modulated respectively.Then, resulting encoded data signal through walsh code modulation is sent in separately the multiplier (or modulo-2 adder) 63,73,83 and 93, at there, they are modulated by pseudo noise (PN) subsequence separately respectively, (these pseudo noises (PN) subsequence produce continuously, its cycle is generally 2 42Have different starting positions in-1 the PN long code sequence), thus frequency spectrum expanded through the code signal of walsh code modulation.Next, be provided to separately multiplier or modulo-2 adder 64,74,84 and 94 respectively through the signal of long code modulation, at there, they are respectively by homophase PN short code sequence PN_I modulation, to produce spread spectrum in-phase signal DSS separately 0I, DSS 1I, DSS 2IAnd DSS 3IThey also are provided to separately multiplier or modulo-2 adder 65,75,85 and 95 respectively, and at there, they are modulated by quadrature phase PN short code sequence PN_Q respectively.The result of quadrature phase PN short code sequence PN_Q modulation is sent to respectively in separately 1/2 chip delay 66,76,86 and 96, to produce spread-spectrum orthogonal phase signal DSS separately 0Q, DSS 1Q, DSS 2QAnd DSS 3QHomophase and quadrature phase short code sequence PN_I and PN_Q generally have the cycle 2 15-1, and they are that the base station that communicates with mobile radio station is peculiar.
In parts 58, the PN long code subsequence that is applied in the channel 0 is sent among the data burst randomizer 69b, and next it produce a control signal after time delay 70, so that can connect power amplifier 50 in needs.
Parts 56 comprise a parts 56a, in these parts, with signal DSS 0I, DSS 1IDSS 2IAnd DSS 3IJust can obtain signal DDSS after being added to finite impulse response shaping filter (FIR_I) 67,77,87 and 97 separately 0I, DDSS 1I, DDSS 2IAnd DDSS 3I, simultaneously, in these parts with signal DSS 0Q, DSS 1Q, DSS 2QAnd DSS 3QJust can obtain signal DDSS after being added to finite impulse response shaping filter (FIR_Q) 68,78,88 and 98 separately 0Q, DDSS 1Q, DDSS 2QAnd DDSS 3QIt is pointed out that FIR_I77 has introduced a scale factor-1, FIR_I87, FIR_Q88 and FIR_Q98 have introduced one and real-valuedly have been Fractional scaling factor, and FIR_I97 has introduced one and real-valuedly is Fractional scaling factor.
Parts 56 also comprise a parts 56b, have made up to its addition resulting signal DDSS 0I, DDSS 0Q, DDSS 1I, DDSS 1Q, DDSS 2I, DDSS 2Q, DDSS 3IAnd DDSS 3QThereby generate combination of numbers signal component DCSS IAnd DCSS QTerm " combination of addition ground " means and comprises the symbol that subtracts each other and/or changed operand before addition.Parts 56b comprises adder 89 and adder 90 as shown in figure, and adder 89 is by the resulting DDSS of addition 2IAnd DDSS 2QAnd the middle spread spectrum in-phase signal IDSS of formation channel 2 2I, adder 90 is passed through from resulting spread-spectrum signal DDSS 2QIn deduct resulting spread-spectrum signal DDSS 2IAnd the middle spread-spectrum orthogonal phase signal IDSS of formation channel 2 2QParts 56b also comprises adder 99 and adder 100, and adder 99 is by the resulting signal DDSS of addition 3IAnd DDSS 3QAnd the middle spread spectrum in-phase signal IDSS of formation channel 3 3I, adder 100 is passed through from resulting spread-spectrum signal DDSS 2IIn deduct resulting spread-spectrum signal from DDSS 2QAnd the middle spread-spectrum orthogonal phase signal IDSS of formation channel 3 3Q
Should be noted that, be actual absolute value among the parts 56a
Figure A0080184500111
Fractional scaling factor introducing and produce by adder 89,90,99 and 100 and combined with the introducing of difference, just make M signal to IDSS 2IAnd IDSS 2QPhase place rotated π/4 radians, make M signal to IDSS 3IAnd IDSS 3QPhase place rotated 3 π/4 radians.
In addition, for channel 1, phase place rotation pi/2 radian is only finished by exchange homophase and quadrature phase component, and this is to have suffered because the in-phase component sign modification that needed before exchange has been bonded to the scale factor-1 of FIR_I77.
After having considered all phase deviations that need, from the homophase of each channel and the part addition in adder 110 and 120 separately respectively of quadrature phase, its output is combination homophase and quadrature phase signal component DCSS separately IAnd DCSS QBecause according to IS-95B, nearly 8 bundled channels is possible, and in fact adder 110 and 120 couples of channel 4-7 have additional input (not shown), and as foregoing, the form with channel 0-4 is the same respectively for they.As shown in the figure, adder 110 received signal DDSS 0I, DDSS 1Q, IDSS 2IAnd IDSS 2QAs its input, and adder 120 received signal DDSS 0Q, DDSS 1I, IDSS 2QAnd IDSS 3QAs its input.In order to keep consequential signal DCSS IAnd DCSS QSuitable dynamic range is arranged, and adder 110 and 120 also receives the onesize control signal on online 115 and 125 respectively.
Should be noted that parts 56 can adopt various ways.Needed fractional scaling factor can be in these parts 56 different positions introduce (for example) at adder 110 and 120 relevant input, and scale factor-1 can be introduced as sign modification before addition.In addition, various additions and subtract each other can change order, further split or combination.For example, adder 89 and 99 can be deleted be fallen, and its function is combined among the adder 110, and adder 99 and 100 can be deleted falls, and its function is combined among the adder 120.In this case, adder 110 and 120 will respectively have 6 inputs, be respectively applied for part of receive channel 0 and 1 and two parts of channel 2 and 3.
Preferablely be, the numerical data that is used for all operations in the parts 58 (numerical data that comprises the FIR filter that will be input to parts 56a) all is the bipolarity single-bit, value is+1, and the output of the FIR filter of parts 56a and comprise that the subsequence numerical data of all back of the output of adder 110 and 120 all is bipolarity 5 bits, its integer span is-15 to+15.
Fig. 3 has provided second kind of embodiment, it seems the same with the embodiment of Fig. 2, different is: the parts of being made up of parts 56a and 56b 56 among Fig. 2 are changed into (it does not comprise the FIR filter by parts 156a among Fig. 3, only introduced needed fractional scaling factor), (portion within it, adder 120 is carrying out changing DDSS before the addition to 156b 1ISymbol so that introduce the factor-1 of needs) parts 156 and additional forming filter FIR_I167 and the FIR_Q168 that form, they receive the bipolarity 5 bits output of each adder 110 and 120 respectively, and form bipolarity 5 bit combination signal DCSS respectively IAnd DCSS QHomophase and the digital FIR filter in the quadrature phase passage 67,68,77,78,87,88,97 and 98 with each channel in the homophase of composite signal among Fig. 3 and digital filter 167 in the quadrature phase passage and 168 alternate figures 2, consequently further reduced complexity, although filter 167 and 168 has adopted the input of 5 bits.
Now, should be noted that purpose of the present invention is met.Though the present invention has been carried out very detailed description, should be noted that within expection idea of the present invention and scope, but may also have many improvements.When explaining appended claims, be appreciated that
A) speech " comprises " and does not get rid of those other unit step outside claim is cited;
B) appear at certain unit mark " " before, not getting rid of has many same dvielements;
C) any reference symbol in the claim does not limit their scope; And
D) some " devices " may be represented by identical structure or function with hardware or software realization.

Claims (10)

1. transmitter installation that in digital code division multiple access (CDMA) wireless communication system, is used for the high data rate multichannel chain-line, wherein represented a plurality of different low data rate services channel distributes in the sinusoidal carrier that one group of phase deviation scope is 0-π in the combination RF signal (CRF) that sends, and comprising:
Be used for forming the device of the combination complex spread spectrum signal of forming by in-phase component (DCSSI or ACSSI) and quadrature phase component (DCSSQ or ACSSQ) in the mode of all phase shifts of introducing represented channel needs; And
A kind of device (144,146,150), be used for the combination complex spread spectrum signal is carried out up-conversion, its method is the signal and the homophase sine wave (sin (act)) multiply each other (144) of deriving from in-phase component (DCSSI or ACSSI), the signal that to derive from quadrature phase component (DCSSQ or ACSSQ) and quadrature phase sine wave (sin (act)) multiply each other (DCSSQ or ACSSQ), and the results added (150) of will multiply each other (144,146) is to form combination RF signal (CRF);
Wherein said a plurality of different low data rate channel is three or more individual channel (channel 0,1,2,3), comprising two or more phase shifts be 0, the individual channel of pi/2 or π radian and one or more phase shifts are not 0, the individual channel of pi/2 or π radian.
2. the device of claim 1, the device that wherein is used to form the combination complex spread spectrum signal comprises:
Be used to form the device (58) of each complex spread spectrum signal of corresponding each channel, wherein each complex spread spectrum signal all is made up of in-phase component (DSS0I, DSS1I, DSS2I and DSS3I) and quadrature phase component (DSS0Q, DSS1Q, DSS2Q and DSS3Q); And
Be used for signal (56a, 156a) that addition ground combination derives from each complex spread spectrum signal of corresponding each channel with the device of the complex spread spectrum signal that forms combination (56b, 156b);
Wherein, from the signal that one or more phase shifts are not 0, each complex spread spectrum signal of the channel (channel 2 and 3) of pi/2 and π radian is derived, be to come the signal that is 0, each complex spread spectrum signal of the channel (channel 0 and 1) of pi/2 and π is derived converted and obtain (56a, 156a) from two or more phase shifts by using relevant fractional scaling factor.
3. the device of claim 2, it can be 0 so that the homophase (DCSSI or ACSSI) of combination spread-spectrum signal and quadrature phase component (DCSSQ or ACSSQ) receive from phase shift respectively that the device (56b) that wherein is used for making up on addition ground is configured to, the part of the signal of the homophase of each complex spread spectrum signal of the channel of pi/2 or π (channel 0 and 1) or any in the quadrature phase component rather than whole two derivation, simultaneously, their receptions are not 0 from phase shift, the part of the signal of the homophase of each complex spread spectrum signal of the channel of pi/2 or π (channel 2 and 3) or whole two derivation of quadrature phase component.
4. the device of claim 2 wherein saidly is not 0, the phase shift of pi/2 or π is exactly π/4 or 3 π/4, and fractional scaling factor has absolute value
5. the device of claim 3 wherein saidly is not 0, the phase shift of pi/2 or π is exactly π/4 or 3 π/4, and fractional scaling factor has absolute value
6. the device of claim 1-5, wherein homophase of each complex spread spectrum signal of each individual channel (DSS0I, DSS1I, DSS2I and DSS3I) and quadrature phase component (DSS0Q, DSS1Q, DSS2Q and DSS3Q) are sent to the input of finite impulse response (FIR) (FIR) filter (67,68,77,78,87,88,97 and 98) separately respectively, and the device (56b) that is used for the combination of addition ground is delivered in this filter output.
7. the device of claim 1-5, homophase of the complex spread spectrum signal of combination wherein (DCSSI) and quadrature phase (DCSSQ) component are sent to the input of finite impulse response (FIR) (FIR) filter (167 and 168), and the device (144,146 and 150) that is used for up-conversion is delivered in this filter output.
8. sending method that in digital code division multiple access (CDMA) wireless communication system, is used for the high data rate multichannel chain-line, wherein represented a plurality of different low data rate services channel distributes in representing by the sine wave that is 0-π one group of phase deviation scope in the combination RF signal (CRF) that sends, and comprising:
Form the combination complex spread spectrum signal of forming by in-phase component (DCSSI or ACSSI) and quadrature phase component (DCSSQ or ACSSQ) in the mode of introducing all phase shifts that represented channel needs; And
The combination complex spread spectrum signal is carried out up-conversion (144,146,150), its method is the signal and the homophase sine wave (sin (act)) multiply each other (144) of deriving from in-phase component (DCSSI or ACSSI), the signal that to derive from quadrature phase component (DCSSQ or ACSSQ) and quadrature phase sine wave (sin (act)) multiply each other (DCSSQ or ACSSQ), and the results added (150) of will multiply each other (144,146) is to form combination RF signal (CRF);
Wherein said a plurality of different low data rate channel is three or more individual channel (channel 0,1,2,3), comprising two or more phase shifts be 0, the individual channel of pi/2 or π radian and one or more phase shifts are not 0, the individual channel of pi/2 or π radian.
9. the method for claim 8, the operation of the complex spread spectrum signal of wherein said formation combination comprises:
Form each complex spread spectrum signal of corresponding each channel, wherein each complex spread spectrum signal all is made up of in-phase component (DSS0I, DSS1I, DSS2I and DSS3I) and quadrature phase component (DSS0Q, DSS1Q, DSS2Q and DSS3Q); And
The complex spread spectrum signal that the signal that making up (56a, 156a) to addition derives from each complex spread spectrum signal of corresponding each channel makes up with formation;
Wherein, from the signal that one or more phase shifts are not 0, each complex spread spectrum signal of the channel (channel 2 and 3) of pi/2 and π radian is derived, be to come the signal that is 0, the single complex spread spectrum signal of the channel (channel 0 and 1) of pi/2 and π is derived converted and obtain from two or more phase shifts by using relevant fractional scaling factor.
10. the method for claim 2, the wherein said operative configuration that is used for addition ground combination (56b, 156b) is such: the homophase of combination spread-spectrum signal and quadrature phase component receive respectively from phase shift be 0, the part of the signal of any rather than whole two derivation of the homophase of the single complex spread spectrum signal of the channel (channel 0 and 1) of pi/2 or π or quadrature phase component, simultaneously, their receive from phase shift be not 0, the part of the signal of whole derivation of the homophase of the single complex spread spectrum signal of the channel (channel 2 and 3) of pi/2 or π or quadrature phase component.
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CN103999383A (en) * 2011-12-15 2014-08-20 瑞典爱立信有限公司 Optical homodyne coherent receiver and method for receiving a multichannel optical signal
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CN103999383B (en) * 2011-12-15 2016-10-19 瑞典爱立信有限公司 For receiving light homodyne coherent receiver and the method for multi-channel optical signal

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