CN114843789A - Circular polarization FP resonant cavity antenna - Google Patents
Circular polarization FP resonant cavity antenna Download PDFInfo
- Publication number
- CN114843789A CN114843789A CN202210388124.6A CN202210388124A CN114843789A CN 114843789 A CN114843789 A CN 114843789A CN 202210388124 A CN202210388124 A CN 202210388124A CN 114843789 A CN114843789 A CN 114843789A
- Authority
- CN
- China
- Prior art keywords
- feed source
- center
- patch
- floor
- medium plate
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Images
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
- H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
- H01Q15/0013—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices working as frequency-selective reflecting surfaces, e.g. FSS, dichroic plates, surfaces being partly transmissive and reflective
- H01Q15/0026—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices working as frequency-selective reflecting surfaces, e.g. FSS, dichroic plates, surfaces being partly transmissive and reflective said selective devices having a stacked geometry or having multiple layers
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/27—Adaptation for use in or on movable bodies
- H01Q1/28—Adaptation for use in or on aircraft, missiles, satellites, or balloons
- H01Q1/288—Satellite antennas
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
- H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
- H01Q15/24—Polarising devices; Polarisation filters
- H01Q15/242—Polarisation converters
- H01Q15/244—Polarisation converters converting a linear polarised wave into a circular polarised wave
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
- H01Q19/06—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using refracting or diffracting devices, e.g. lens
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
- H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
- H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
- H01Q9/04—Resonant antennas
- H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
- H01Q9/0428—Substantially flat resonant element parallel to ground plane, e.g. patch antenna radiating a circular polarised wave
Landscapes
- Physics & Mathematics (AREA)
- Engineering & Computer Science (AREA)
- Astronomy & Astrophysics (AREA)
- General Physics & Mathematics (AREA)
- Remote Sensing (AREA)
- Aviation & Aerospace Engineering (AREA)
- Waveguide Aerials (AREA)
Abstract
A circularly polarized FP resonant cavity antenna comprises a circularly polarized conversion super-structured surface, wherein a super-structured surface unit of the circularly polarized conversion super-structured surface comprises a lower dielectric plate of an upper dielectric plate, a metal floor is arranged between the upper dielectric plate and the lower dielectric plate, a radiation patch is arranged on the upper dielectric plate and is a square with two opposite angles cut off, the center of a first metalized through hole on the radiation patch is superposed with the center of the super-structured surface unit and is not superposed with the center of the radiation patch, a receiving patch is arranged on the lower dielectric plate, the center of a second metalized through hole on the receiving patch is superposed with the center of the super-structured surface unit and is not superposed with the center of the receiving patch, a through hole is arranged on the metal floor, and the centers of the first metalized through hole, the second metalized through hole and the through hole are superposed; the rotation angle of the radiation patch is 0-360 degrees; a floor disposed below the surface of the linear-circular polarization conversion superstructure; and the linear polarization feed source is positioned between the linear circular polarization conversion superstructure surface and the floor. The antenna can realize beam deflection and circularly polarized radiation.
Description
Technical Field
The invention belongs to the technical field of microwave communication, and particularly relates to a circularly polarized Fabry-Perot resonant cavity antenna.
Background
A Fabry-Perot (FP) resonator antenna is a high gain antenna which can generate a very high gain with a simple structure, and thus is applied in many cases. Particularly, with the rise of printed electromagnetic periodic structures, the FP resonant cavity antenna designed by using the printed electromagnetic periodic structures as Partial Reflection Surface (PRS) coatings has the characteristics of simple structure, stable performance and the like, and greatly promotes the development of the FP resonant cavity antenna in the directions of easy processing, low profile, low manufacturing cost and the like. However, most of the existing FP resonant cavity antennas are linearly polarized radiation, and realizing circularly polarized radiation is a difficult point and a key point of research of the FP resonant cavity antennas. Due to the limitation of the resonance characteristics of the resonant cavity antenna, the radiation direction of the resonant cavity antenna is relatively fixed, beam deflection is difficult to realize, and beam deflection of the circularly polarized FP resonant cavity antenna is more difficult.
Disclosure of Invention
The invention aims to provide a circularly polarized FP resonant cavity antenna capable of realizing beam deflection.
In order to achieve the purpose, the invention adopts the following technical solutions:
a circularly polarized FP cavity antenna, comprising; the line-circular polarization conversion ultrastructure surface comprises a plurality of ultrastructure surface units, each ultrastructure surface unit comprises an upper medium plate and a lower medium plate which are stacked up and down, a metal floor is arranged between each upper medium plate and each lower medium plate, a radiation patch for radiating circular polarization electromagnetic waves is arranged on the upper surface of each upper medium plate, each radiation patch is a square with two opposite corners cut off, a first metalized through hole is formed in each radiation patch, the center of each first metalized through hole is coincided with the center of each ultrastructure surface unit and is not coincided with the center of each radiation patch, a receiving patch which is used for receiving the linear polarization electromagnetic waves and is correspondingly arranged on the lower surface of each lower medium plate, a second metalized through hole is arranged on each receiving patch, and the center of each second metalized through hole is coincided with the center of the ultrastructure surface unit and is not coincided with the center of the receiving patch The metal floor is provided with a through hole, and the centers of the first metalized via hole, the second metalized via hole and the through hole are overlapped; the rotation angle of the radiation patch is 0-360 degrees; the floor is arranged below the linear and circular polarization conversion superstructure surface at intervals, and the linear and circular polarization conversion superstructure surface and the floor form a resonant cavity; a linear polarization feed located between the linear circular polarization converting superstructure surface and the floor.
As an optional implementation manner of the circular polarized FP resonator antenna of the present invention, the radiation patch is an axisymmetric pattern, and the symmetry axis is a diagonal line of a square where the radiation patch is located.
As an alternative embodiment of the circularly polarized FP cavity antenna of the present invention, the ratio of the area of the diagonal of the cut-out of the radiating patch to the area of the radiating patch does not exceed 0.2.
As an optional implementation manner of the circular polarized FP resonator antenna according to the present invention, a distance between a center of the first metalized via and a center of the radiation patch is 0.5mm to 0.9 mm.
As an optional implementation manner of the circular polarized FP resonator antenna according to the present invention, a distance between a center of the second metalized via and a center of the receiving patch is 1.1mm to 1.5 mm.
As an optional implementation manner of the circular polarized FP resonator antenna of the present invention, the linear polarized feed source is a slot-coupled patch antenna.
As an optional implementation mode of the circularly polarized FP resonant cavity antenna, the linearly polarized feed source comprises an upper layer feed source dielectric plate, a lower layer feed source dielectric plate, a feed source floor, a feed source radiation patch and a feed line, the feed source radiation patch is arranged on the upper surface of the upper feed source dielectric slab, the center of the feed source radiation patch is superposed with the center of the upper feed source dielectric slab, the feed line is arranged on the lower surface of the lower feed source dielectric plate, the feed source floor is arranged between the upper feed source dielectric plate and the lower feed source dielectric plate which are stacked up and down, the feed source floor is provided with a coupling gap, the coupling gap is parallel to the side edge of the feed source floor and passes through the center of the feed source floor, the feed line extends to the center of the lower feed source dielectric plate from the edge of one side of the lower feed source dielectric plate, and the feed line is perpendicular to the coupling gap.
As an optional implementation manner of the circular polarized FP cavity antenna of the present invention, the feed source floor is the floor.
As an optional implementation manner of the circular polarized FP resonator antenna of the present invention, the feed source radiation patch is a square metal patch.
As an optional implementation manner of the circular polarized FP cavity antenna according to the present invention, the receiving patch is a square metal patch.
According to the technical scheme, the polarization conversion superstructure surface capable of flexibly regulating and controlling the polarization characteristics of transmitted or reflected electromagnetic waves is designed, the reflection phase and the transmission polarization of the superstructure surface can be independently regulated and controlled, the polarization conversion is carried out on the transmitted electromagnetic waves while the reflectivity is high, linear polarization waves are converted into circular polarization waves, the linear circular polarization conversion superstructure surface is used as a partial reflection surface of an FP resonant cavity antenna, the FP resonant cavity antenna and a linear polarization feed source form the FP resonant cavity antenna, the FP resonant cavity antenna can realize circular polarization radiation while keeping high gain characteristics, good high gain circular polarization radiation characteristics are realized, and meanwhile, the beam deflection of the circular polarization FP resonant cavity antenna can be realized by regulating the rotation angle of the radiation patches of each superstructure surface unit. The antenna can be well applied to the field of satellite communication.
Drawings
FIG. 1 is a schematic structural diagram of an FP resonant cavity antenna according to an embodiment of the present invention;
FIG. 2a is an exploded view of a nanostructured surface unit according to an embodiment of the present invention;
fig. 2b is a schematic structural diagram of a radiation patch according to an embodiment of the present invention;
FIG. 2c is a schematic structural diagram of a receiving patch according to an embodiment of the present invention;
FIG. 2d is a schematic structural diagram of a metal floor according to an embodiment of the present invention;
fig. 2e is a schematic view of the upper surface of the metamaterial surface made up of metamaterial surface elements with the radiating patches not rotated;
FIG. 2f is a schematic view of the lower surface of the microstructured surface;
fig. 3a and 3b are S-parameter diagrams of a metamaterial surface consisting of metamaterial surface elements with the radiating patches not rotated;
FIG. 4 is a top view of a linearly polarized feed according to an embodiment of the present invention;
FIG. 5a is a schematic view of the radiation patch when not rotated;
fig. 5b is a schematic view of the radiation patch rotated by β °;
FIG. 6 is a graph of the change in transmission phase of the unit of the superstructure surface when the radiation patch is rotated by different angles about the y-axis;
fig. 7a and 7b are graphs of the variation of the S-parameter of the metamaterial surface element with the rotation angle α of the radiating patch;
FIGS. 8a, 8b and 8c illustrate an embodiment of an antenna
And
transmission phase distribution graphs required by the surfaces of the ultra-structures during 60-degree beam deflection are realized in three planes;
FIGS. 9a, 9b and 9c illustrate an embodiment of an antenna, respectively
And
a top view of the surface of the superstructure when a 60 ° beam deflection is achieved in three planes;
FIGS. 10 a-10 f illustrate an embodiment of an antenna
And
directional diagrams and axial ratio diagrams when beams of 30 degrees, 60 degrees and 80 degrees are deflected are respectively realized in three planes;
FIGS. 11 a-11 d are diagrams of embodiments of an antenna
And
the 60 DEG wave beam deflection directional diagram is realized in three planes.
The present invention will be described in further detail with reference to the drawings and examples.
Detailed Description
The invention will be described in detail below with reference to the accompanying drawings, wherein for the purpose of illustrating embodiments of the invention, the drawings showing the structure of the device are not to scale but are partly enlarged, and the schematic drawings are only examples, and should not be construed as limiting the scope of the invention. It should be noted that the drawings are in simplified form and are not to precise scale, which is provided for the purpose of facilitating and clearly facilitating the description of the embodiments of the present invention. Meanwhile, in the description of the present application, the terms "first", "second", and the like are used only for distinguishing the description, and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated; the terms "front," "back," "bottom," "upper," "lower," and the like refer to an orientation or positional relationship relative to an orientation or positional relationship shown in the drawings, which is for convenience and simplicity of description, and do not indicate or imply that the referenced device or element must have a particular orientation, be constructed and operated in a particular orientation, and thus should not be construed as limiting the present invention.
A metamaterial with a two-dimensional form is a metamaterial with a Metasurface (MS for short), and flexible regulation and control of characteristics such as electromagnetic wave phase, amplitude and polarization are achieved by reasonably arranging periodic structure units with sub-wavelengths on the surface of a medium. The invention designs a linear-circular polarization conversion superstructure surface which can perform polarization conversion on transmitted electromagnetic waves, and a resonant cavity antenna is formed by the linear polarization feed source, can convert linear polarization waves into circular polarization waves, and realizes beam deflection by a radiation patch rotating a certain angle.
As shown in fig. 1, the circular polarization FP resonant cavity antenna of the present embodiment includes a linear circular polarization conversion superstructure surface 1, a linear polarization feed source 2, and a floor (2-3), where the linear circular polarization conversion superstructure surface 1 and the floor form a resonant cavity. The floor of the resonant cavity antenna of the embodiment is also the floor of the linear polarization feed source 2, that is, the linear polarization feed source 2 is arranged on the floor, and the floor of the linear polarization feed source 2 is also the floor of the resonant cavity antenna, so that the structure of the antenna can be simplified. The resonant cavity is excited by the linear polarization feed source 2, the linear polarization feed source 2 radiates linearly polarized electromagnetic waves, linear polarization resonance is formed inside the resonant cavity, the linear polarization conversion superstructure surface 1 has the capacity of converting the linear polarized waves into the circular polarized waves while providing high reflectivity, and the linearly polarized electromagnetic waves in the resonant cavity are converted into the circular polarized waves when reaching the outside of the resonant cavity through the linear polarization conversion superstructure surface 1, so that the antenna realizes high-gain circular polarized radiation.
The linear circular polarization conversion metamaterial surface 1 of the present embodiment includes a plurality of metamaterial surface units 1-1 (fig. 2e) arranged in an array, and the structure of each of the metamaterial surface units 1-1 is the same. As shown in fig. 2a, the super-structure surface unit 1-1 includes an upper dielectric slab 1-1a, a lower dielectric slab 1-1b, a radiation patch 1-1c, a reception patch 1-1d, and a metal floor 1-1 e. The upper-layer dielectric slab 1-1a and the lower-layer dielectric slab 1-1b are stacked up and down, the metal floor 1-1e is arranged between the upper-layer dielectric slab 1-1a and the lower-layer dielectric slab 1-1b, the radiation patch 1-1c is arranged on the upper surface of the upper-layer dielectric slab 1-1a, the receiving patch 1-1d is arranged on the lower surface of the lower-layer dielectric slab 1-1b, the receiving patch 1-1d and the radiation patch 1-1c are correspondingly arranged, namely, one receiving patch 1-1d is correspondingly arranged below one radiation patch 1-1 c. The thickness t of the upper dielectric plate 1-1a and the lower dielectric plate 1-1b in this embodiment is 1.524mm, and the side lengths p are both 10mm, which is the unit period of the metamaterial surface unit 1-1. F4B board with relative dielectric constant of 2.65 is adopted as the upper and lower dielectric boards.
As shown in fig. 2b, the radiation patch 1-1c of the present embodiment is a square metal patch from which two opposite corners are cut, the cut regions at each of the opposite corners (the regions shown by the dotted lines in fig. 2b, i.e., the areas of the cut opposite corners) are all isosceles right triangles, and the ratio of the area of the cut region to the area of the radiation patch 1-1c is not more than 0.2, i.e., the ratio of the areas of the two isosceles triangles and the radiation patch (the gray filled region in fig. 2 b) is not more than 0.2. The radiation patches 1-1c are enabled to radiate circularly polarized electromagnetic waves by cutting off two opposite corners of a square radiation patch. The radiation patches 1-1c are axisymmetric patterns, and the symmetry axis is the diagonal of the square where the radiation patches are located. A first metallized via a is provided on the radiating patch 1-1 c. The center of the first metalized via hole a coincides with the center of the super-structure surface unit 1-1 (the upper dielectric plate 1-1a), but the center of the first metalized via hole a does not coincide with the center of the radiation patch 1-1c (black point in fig. 2 b), the center of the first metalized via hole a and the center of the radiation patch 1-1c are both located on the middle line of the super-structure surface unit 1-1 in the y-axis direction, and the distance d between the center of the first metalized via hole a and the center of the radiation patch 1-1c 2 Is 0.5 mm-0.9 mm.
As shown in fig. 2c, the receiving patch 1-1d of the present embodiment is square, and the receiving patch 1-1d is used for receiving linearly polarized electromagnetic waves. The receiving patches 1-1d are provided with second metallized through holes b, and the radiation patches 1-1c and the receiving patches 1-1d are connected through the metallized through holes. The center of the second metallized via hole b coincides with the center of the super-structure surface unit 1-1c (the lower dielectric plate 1-1b), but the center of the second metallized via hole b does not coincide with the center of the receiving patch 1-1d (black point in fig. 2 c), the center of the second metallized via hole b and the center of the receiving patch 1-1d are both located on the middle line of the super-structure surface unit 1-1 in the y-axis direction, and the second metallized via hole b and the receiving patch 1-1d are both located on the middle line of the super-structure surface unit 1-1 in the y-axis directionTo change the distance d between the center of the via b and the center of the receiving patch 1-1d 1 Is 1.1 mm-1.5 mm. The centers of the receiving patch 1-1d and the radiating patch 1-1c are deviated from the center of the super-structure surface unit 1-1 towards the negative direction of the y axis to realize impedance matching, and d is adjusted 1 And d 2 The reflection amplitude (reflectivity) of the superstructure surface element can be adjusted.
As shown in FIG. 2d, the metal floorboards 1-1e are provided with through-holes c. The size of the metal floor 1-1e is the same as that of the upper dielectric slab 1-1a and the lower dielectric slab 1-1 b. The centers of the first metallized via hole a, the second metallized via hole b and the through hole c are overlapped. The electromagnetic waves received by the receiving patches 1-1d are coupled to the radiating patches 1-1c through the metalized through holes and the through holes on the metal floor.
As shown in fig. 2b and 2c, for convenience of description, the side length of the square (square without cutting off two opposite corners) where the radiation patches 1-1c are located is defined as the side length w of the radiation patch 2 The side length of the receiving patch 1-1d is w 1 . W of the present embodiment 2 ＝7.2mm，w 1 ＝6.78mm、d 2 ＝0.7mm、d 1 1.3mm, the side length of the right-angled side of the isosceles right triangle area where the radiation patch 1-1c is cut off is 2.65mm, and the area of the radiation patch 1-1c is (7.2 × 7.2) - (2.65 × 2.65) ═ 44.8175mm 2 The area of the two isosceles right triangle areas that are cut off is 7.0225, 2.65 × 2.65. Fig. 2e and 2f are schematic diagrams of the upper and lower surfaces of a metamaterial surface consisting of metamaterial surface elements with non-rotated radiating patches, the S-parameters of which are shown in fig. 3a and 3 b. As can be seen from fig. 3a and 3b, the reflection amplitude of the super-structure surface unit reaches 0.9 at 10GHz, the right-hand circular polarization amplitude of the electromagnetic wave transmitted by the super-structure surface unit reaches the maximum, and the left-hand circular polarization amplitude is almost 0, and the super-structure surface unit realizes the conversion from the linear polarized wave to the circular polarized wave.
The linearly polarized feed source 2 of the embodiment adopts a slot coupling patch antenna, and as shown in fig. 1 and 4, the linearly polarized feed source 2 comprises an upper feed source dielectric plate 2-1, a lower feed source dielectric plate 2-2, a feed source floor 2-3, a feed source radiation patch 2-4 and a feed line 2-5. The feed source radiation patch 2-4 is arranged on the upper layer feedThe upper surface of the source dielectric plate 2-1, and the center thereof is superposed with the center of the upper layer feed source dielectric plate 2-1. The feed line 2-5 is arranged on the lower surface of the lower feed source dielectric plate 2-2, the feed source floor 2-3 is arranged between the upper feed source dielectric plate 2-1 and the lower feed source dielectric plate 2-2 which are stacked up and down, and a coupling gap s is formed in the feed source floor 2-3 so as to realize coupling feed from the feed line 2-5 to the feed source radiation patch 2-4. The coupling gap s is parallel to the side of the feed source floor 2-3 and passes through the center of the feed source floor 2-3 (the y axis is perpendicular to the coupling gap s). The feed source radiation patches 2-4 are square metal patches, and the feed lines 2-5 are metal feed lines. The feed source radiation patches 2-4 of the embodiment are squares with side length Lp of 7.2mm, the length Ls of the coupling slot s is 5.5mm, the width is 1.2mm, and the width w of the feed line 2-5 0 Is 2.1 mm. The feed line 2-5 extends to the center of the lower feed source dielectric plate 2-2 from one side edge of the lower feed source dielectric plate 2-2, and the feed line 2-5 is perpendicular to the coupling gap s.
When the radiation patch 1-1c is rotated around the y-axis, the transmission phase of the metamaterial surface elements changes with the rotation angle of the radiation patch. For convenience of description, an angle between the symmetry axis of the radiation patch and a center line of the super structure surface unit in the y-axis direction (i.e., the y-axis) is defined as a rotation angle α of the radiation patch. Fig. 5a and 5b are schematic views of radiation patches with different rotation angles, respectively, and the radiation patch of fig. 5b is rotated counterclockwise by β ° with respect to the radiation patch of fig. 5a, i.e., the difference between the rotation angles of the radiation patches in fig. 5a and 5b is β °. The transmission phase of the super-structure surface unit is changed by rotating the radiation patch, and the transmission phase distribution of the super-structure unit on the super-structure surface is designed according to requirements, so that the wave beam of the FP resonant cavity antenna can point to a specific direction, and the wave beam deflection is realized.
Fig. 6 shows the variation of the transmission phase of the metamaterial surface elements when the radiation patch shown in fig. 5a is rotated by different angles (β), and it can be seen from fig. 6 that the transmission phase of the metamaterial surface elements varies according to the rotation of the radiation patch, and the variation of the transmission phase is the same as the angle of rotation. Fig. 7a and 7b are graphs of the variation of the S-parameter of the metamaterial surface unit with the rotation angle of the radiation patch, respectively, fig. 7a is a graph of the variation of the transmission coefficient of the metamaterial surface unit, and fig. 7b is a graph of the variation of the reflection coefficient of the metamaterial surface unit. As can be seen from fig. 7a and 7b, the radiation patch rotates by one circle in the range of 0 to 360 °, the transmission phase variation range of the nanostructure surface unit also covers 360 °, but the transmission amplitude, the reflection amplitude and the reflection phase of the nanostructure surface unit are all kept unchanged, so that the transmission phase of the nanostructure surface composed of the nanostructure surface units can be adjusted while the reflection coefficient is kept unchanged, and the antenna can obtain the beam deflection effect by adjusting the transmission phase of each nanostructure surface unit on the nanostructure surface.
This embodiment is to make the FP resonant cavity antenna at
And
the beam deflection of 60 degrees is realized in three planes,
is the plane of the x-axis,
is the plane of the y-axis,
is a plane in the middle of the included angles of the x axis and the y axis, firstly, the transmission phase distribution of the super-structure surface is calculated,
and θ is the three dimensional polar coordinate of the beam direction in space
The expression (2) in (1),
where k is an electromagnetic waveP is the cell period of the unit with the super-structure surface, and the phase difference alpha of the adjacent units of the transmission phase of the super-structure surface in the x direction and the y direction is calculated according to the two formulas x And alpha y Setting the rotation angle of the radiation patch of the metamaterial surface unit at the center of the metamaterial surface as 0 degree, determining the transmission phase of the metamaterial surface unit after determining the structure (shape and size) of the metamaterial surface unit, and determining the transmission phase according to the transmission phase of the metamaterial surface unit at the center and the phase difference alpha of the adjacent units x And alpha y Calculating the transmission phases of all the other ultrastructural surface units; then, the rotation angle of the radiation patch of each unit of the metamaterial surface on the metamaterial surface is determined according to the distribution of the transmission phase at each position of the metamaterial surface, and the relationship between the transmission phase and the rotation angle is obtained according to simulation, as shown in fig. 7 a. FIG. 8a, FIG. 8b and FIG. 8c are the antenna in
And
transmission phase distribution graphs required by the surfaces of the ultra-structures during 60-degree beam deflection are realized in three planes; FIGS. 9a, 9b and 9c show the antenna in
And
a top view of the surface of the superstructure while achieving a 60 ° beam deflection in three planes.
The antenna of the embodiment is simulated by CST electromagnetic simulation software, and the directional pattern and axial ratio characteristics of the antenna at 10GHz are contrastingly analyzed. 10 a-10 f are graphs showing simulation results of antenna patterns and axial ratios, where FIGS. 10a and 10b are graphs
Plane realizes 30 DEG, 60 DEG and 80 DEG wave beam deflectionThe folding directional diagram and axial ratio diagram, and FIG. 10c and FIG. 10d are
Directional diagram and axial ratio diagram when the plane realizes beam deflection of 30 degrees, 60 degrees and 80 degrees, and fig. 10e and 10f are
The planes implement patterns and axial ratio maps at 30 °, 60 ° and 80 ° beam deflections. As can be seen from fig. 10a to 10f, the antenna of the embodiment exhibits excellent beam deflection effects in three planes, and the beam deflection angles of 30 ° and 60 ° are almost the same as theoretically calculated, while the beam deflection angles of 80 ° are all smaller than the designed 80 °, and only reach about 75 °. Meanwhile, the axial ratio of the antenna is less than 3dB in the main beam direction of the antenna. The three-dimensional directional patterns of the antenna when the beam is deflected by 60 degrees in three planes are shown in fig. 11a to 11d, and as can be seen from fig. 11a to 11d, the embodiment antenna still keeps a better beam shape when the beam deflection is realized.
The circularly polarized FP resonant cavity antenna is formed by the linearly circularly polarized conversion super-structured surface and the linearly polarized feed source antenna, circularly polarized radiation can be realized by the linearly circularly polarized conversion surface, and beams of the antenna can point to different directions by arranging the super-structured surface units of the radiation patches with different rotation angles, namely by designing the transmission phase distribution of the units on the super-structured surface, so that the circularly polarized FP resonant cavity antenna can realize two-dimensional beam deflection, the maximum deflection angle can reach 75 degrees, and a good beam shape is kept when the beam deflection is realized. The circularly polarized transmission phase of the super-structure surface unit changes along with the rotation of the radiation patch, the change amount of the transmission phase of the super-structure surface unit corresponds to the rotation angle of the radiation patch, the radiation patch rotates for a circle, the transmission phase of the super-structure surface unit can realize 360-degree coverage, and the reflection amplitude and the phase of the super-structure surface unit are not influenced while the transmission phase of the super-structure surface unit changes.
Although the present invention has been described with reference to a preferred embodiment, it should be understood that various changes, substitutions and alterations can be made herein without departing from the spirit and scope of the invention as defined by the appended claims.
Claims (10)
1. A circularly polarized FP resonant cavity antenna, comprising;
the line-circular polarization conversion ultrastructure surface comprises a plurality of ultrastructure surface units, each ultrastructure surface unit comprises an upper medium plate and a lower medium plate which are stacked up and down, a metal floor is arranged between each upper medium plate and each lower medium plate, a radiation patch for radiating circular polarization electromagnetic waves is arranged on the upper surface of each upper medium plate, each radiation patch is a square with two opposite corners cut off, a first metalized through hole is formed in each radiation patch, the center of each first metalized through hole is coincided with the center of each ultrastructure surface unit and is not coincided with the center of each radiation patch, a receiving patch which is used for receiving the linear polarization electromagnetic waves and is correspondingly arranged on the lower surface of each lower medium plate, a second metalized through hole is arranged on each receiving patch, and the center of each second metalized through hole is coincided with the center of the ultrastructure surface unit and is not coincided with the center of the receiving patch The metal floor is provided with a through hole, and the centers of the first metalized via hole, the second metalized via hole and the through hole are overlapped; the rotation angle of the radiation patch is 0-360 degrees;
the floor is arranged below the linear and circular polarization conversion superstructure surface at intervals, and the linear and circular polarization conversion superstructure surface and the floor form a resonant cavity;
a linear polarization feed located between the linear circular polarization converting superstructure surface and the floor.
2. The circularly polarized FP resonator antenna of claim 1, wherein: the radiation patches are in axisymmetric patterns, and the symmetry axis is the diagonal line of the square where the radiation patches are located.
3. The circularly polarized FP resonator antenna of claim 1, wherein: the ratio of the area of the diagonal corners from which the radiation patch is cut out to the area of the radiation patch does not exceed 0.2.
4. The circularly polarized FP resonator antenna of claim 1, wherein: the distance between the center of the first metalized through hole and the center of the radiation patch is 0.5 mm-0.9 mm.
5. The circularly polarized FP resonator antenna of claim 1, wherein: the distance between the center of the second metalized via hole and the center of the receiving patch is 1.1 mm-1.5 mm.
6. The circularly polarized FP resonator antenna of claim 1, wherein: the linear polarization feed source is a slot coupling patch antenna.
7. The circularly polarized FP resonator antenna of claim 1, wherein: the linear polarization feed source comprises an upper feed source medium plate, a lower feed source medium plate, a feed source floor, a feed source radiation patch and a feed line, wherein the feed source radiation patch is arranged on the upper surface of the upper feed source medium plate and the center of the upper feed source medium plate are coincided with the center of the upper feed source medium plate, the feed line is arranged on the lower surface of the lower feed source medium plate, the feed source floor is arranged between the upper feed source medium plate and the lower feed source medium plate which are stacked up and down, a coupling gap is formed in the feed source floor, the coupling gap is parallel to the side edge of the feed source floor and passes through the center of the feed source floor, and the feed line extends to the center of the lower feed source medium plate from one side edge of the lower feed source medium plate and is perpendicular to the coupling gap.
8. The circularly polarized FP resonator antenna of claim 8, wherein: the feed source floor is the floor.
9. The circularly polarized FP resonator antenna of claim 1, wherein: the feed source radiation patch is a square metal patch.
10. The circularly polarized FP resonator antenna of claim 1, wherein: the receiving patch is a square metal patch.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202210388124.6A CN114843789A (en) | 2022-04-13 | 2022-04-13 | Circular polarization FP resonant cavity antenna |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202210388124.6A CN114843789A (en) | 2022-04-13 | 2022-04-13 | Circular polarization FP resonant cavity antenna |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN114843789A true CN114843789A (en) | 2022-08-02 |
Family
ID=82563865
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202210388124.6A Pending CN114843789A (en) | 2022-04-13 | 2022-04-13 | Circular polarization FP resonant cavity antenna |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN114843789A (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116581546A (en) * | 2023-07-13 | 2023-08-11 | 山西大学 | Low-profile dual-frequency Fabry-Perot resonant cavity antenna |
-
2022
- 2022-04-13 CN CN202210388124.6A patent/CN114843789A/en active Pending
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116581546A (en) * | 2023-07-13 | 2023-08-11 | 山西大学 | Low-profile dual-frequency Fabry-Perot resonant cavity antenna |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN109742556B (en) | Broadband circularly polarized millimeter wave multi-feed-source multi-beam lens antenna | |
| Encinar | Design of two-layer printed reflectarrays using patches of variable size | |
| CN111864385B (en) | Dual-beam dual-circular polarization resonant cavity antenna based on super surface | |
| CN109818155B (en) | Dual-circular polarization millimeter wave reflective array antenna with independently controllable wave beams | |
| CN110911831B (en) | Double-frequency circularly polarized planar transmission array antenna adopting single-wire polarized feed source | |
| WO2022027950A1 (en) | Millimeter-wave dual circularly polarized lens antenna and electronic device | |
| CN112201944B (en) | FP resonant cavity antenna based on super-structure surface | |
| CN110911830B (en) | Passive frequency scanning Fabry-Perot resonant cavity antenna | |
| CN111430936A (en) | 5G MIMO multi-beam antenna based on super surface | |
| EP1508940A1 (en) | Radiation controller including reactive elements on a dielectric surface | |
| Gao et al. | Low-Profile Wideband CTS Array Using Substrate-Integrated Waveguide Technology for $ K $-Band Applications | |
| CN113097736B (en) | Novel frequency and wave beam reconfigurable antenna | |
| CN114843789A (en) | Circular polarization FP resonant cavity antenna | |
| Tamura et al. | High-impedance surface-based null-steering antenna for angle-of-arrival estimation | |
| Huang et al. | All 3-D printed antennas based on phase velocity control for beam steering and size reduction with low cost | |
| CN112636005B (en) | Circular polarization folding reflection array antenna of full integrated wide angle scanning | |
| Fazaelifar et al. | A circular polarized reflectarray antenna with electronically steerable beam and interchangeable polarizations | |
| CN109216933B (en) | Axial compression two-dimensional planar lens antenna | |
| Sangmahamd et al. | A Metasurface-Based Electronically Reconfigurable and Dual-Polarized Reflectarray Antenna for Beam-Steering Applications | |
| Huang et al. | An array of two periodic leaky-wave antennas with sum and difference beam scanning for application in target detection and tracking | |
| Wei et al. | Design of a variable inclination continuous transverse stub array | |
| CN114759359B (en) | Novel single-layer broadband circularly polarized reflection array antenna | |
| Massaccesi et al. | 3D-Printed Wideband Perforated Dielectric-Only Reflectarray in Ka-band | |
| CN216529345U (en) | Circularly polarized multilayer microstrip antenna unit and three-dimensional array thereof | |
| WO2023273600A1 (en) | Lens unit, lens array, and array antenna |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination |