WO2024254984A1 - 双圆极化反射阵天线及其辐射波束独立控制方法 - Google Patents

双圆极化反射阵天线及其辐射波束独立控制方法 Download PDF

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Publication number
WO2024254984A1
WO2024254984A1 PCT/CN2023/114643 CN2023114643W WO2024254984A1 WO 2024254984 A1 WO2024254984 A1 WO 2024254984A1 CN 2023114643 W CN2023114643 W CN 2023114643W WO 2024254984 A1 WO2024254984 A1 WO 2024254984A1
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printed metal
circularly polarized
shaped printed
metal strip
double
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English (en)
French (fr)
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李波
徐衍昕
常玉梅
韩叶
祝雷
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Nanjing University of Posts and Telecommunications
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Nanjing University of Posts and Telecommunications
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/002—Protection against seismic waves, thermal radiation or other disturbances, e.g. nuclear explosion; Arrangements for improving the power handling capability of an antenna
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/14—Reflecting surfaces; Equivalent structures
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/14—Reflecting surfaces; Equivalent structures
    • H01Q15/18—Reflecting surfaces; Equivalent structures comprising plurality of mutually inclined plane surfaces, e.g. corner reflector
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/24—Polarising devices; Polarisation filters 
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H01Q19/106—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces using two or more intersecting plane surfaces, e.g. corner reflector antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/34—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Definitions

  • the invention belongs to the technical field of radar communication, and in particular relates to a dual circularly polarized reflectarray antenna and a method for independently controlling radiation beams thereof.
  • satellites with multi-beam payloads have been widely developed.
  • One of the key challenges in designing, developing and launching such satellites is to handle the large number of antennas required for the mission.
  • Such satellites usually use a four-color frequency/polarization multiplexing scheme, so designing a dual circularly polarized reflectarray antenna at the same frequency can effectively reduce the number of antennas required for the satellite.
  • the reflectarray antenna consists of a horn feed and a reflectarray. It has the advantages of high gain and no need for a complex feeding network, and has great research value. Its working mechanism is: the reflectarray with a phase shifting function converts the spherical wave from the feed into a plane wave and radiates it outward, thus achieving radiation performance with high gain.
  • the horizontal linear polarized wave and the vertical linear polarized wave are reflected respectively through a reflection array that reflects the horizontal linear polarized wave and transmits the vertical linear polarized wave and a parabolic reflector. Then, the two reflected linear polarized waves are converted into circularly polarized wave output through a linear-circular polarization converter.
  • a linear-circular polarization converter In order to achieve the output of left-hand circularly polarized wave and right-hand circularly polarized wave at different angles, different angles need to be built between the components, which makes the processing very difficult.
  • the technical problem to be solved by the present invention is to provide a dual circularly polarized reflectarray antenna with independently controllable radiation beams.
  • a reflection unit is formed by two dielectric substrates and two groups of "S"-shaped printed metal strips, and then a reflection array is formed to form a dual circularly polarized reflectarray antenna.
  • the antenna has a simple structure and, while ensuring good radiation performance of the antenna, can simultaneously reflect left-handed circularly polarized waves and right-handed circularly polarized waves, and can independently control their radiation beams.
  • a dual circularly polarized reflectarray antenna comprises a circularly polarized antenna feed for transmitting spherical electromagnetic waves and a dual "S"-shaped printed metal strip reflectarray for receiving spherical electromagnetic waves and reflecting them into plane waves; the dual "S"-shaped printed metal strip reflectarray is composed of a plurality of dual "S"-shaped printed metal strip reflector units arranged in an array.
  • the circular polarization antenna feed is oriented toward the double “S” shaped printed metal strip reflective array along the -z direction and is located at the phase shift focus of the double “S” shaped printed metal strip reflective array.
  • the double "S"-shaped printed metal strip reflective unit includes two vertically orthogonal dielectric substrates, each of which is provided with two symmetrical semi-S-shaped printed metal strips; the two dielectric substrates are assembled by plugging to form two groups of cascaded "S"-shaped printed metal strips.
  • the first group of “S”-shaped printed metal strips and the second group of “S”-shaped printed metal strips have the same size, which is the working center frequency wavelength.
  • the first group of "S"-shaped printed metal strips reflects left-handed circularly polarized waves and is located near one end of the circularly polarized antenna feed source, and the second group of "S"-shaped printed metal strips reflects right-handed circularly polarized waves and is located far from one end of the circularly polarized antenna feed source.
  • Step 1 Calculate the reflection phase.
  • the specific formula is:
  • i-th double “S” type printed metal strip reflector unit i ranges from 1 to M ⁇ N; k is the propagation constant in free space; R i is the distance from the circularly polarized antenna feed source 1 to the i-th double “S” type printed metal strip reflector unit; is the position vector of the i-th double “S”-shaped printed metal strip reflector unit; is the direction in which the antenna radiates the main beam; is a phase constant that represents the required phase shift value for the double “S” type printed metal strip reflective array.
  • Step 2 The relationship between the position of the “S”-shaped printed metal strip on the dielectric substrate and the reflection phase is:
  • dz and dz1 represent the relative positions of two groups of “S”-shaped printed metal strips on the dielectric substrate.
  • the double "S” shaped printed metal strip reflective units are arranged in an array, and the specific arrangement method includes: arranging a plurality of double “S” shaped printed metal strip reflective units in parallel in sequence along the x direction, and stacking a plurality of double "S” shaped printed metal strip reflective units in sequence along the y direction.
  • the distance between the “S”-shaped printed metal strips between adjacent double “S”-shaped printed metal strip reflective units arranged in parallel in the x-direction is recorded as the first distance.
  • the distance between the "S"-shaped printed metal strips between adjacent double “S”-shaped printed metal strip reflective units stacked in the y direction is recorded as the second distance.
  • the first distance is equal to the second distance.
  • the present invention also proposes a method for independently controlling the radiation beam of a dual circularly polarized reflectarray antenna.
  • the incident electromagnetic wave is a left-handed circularly polarized wave
  • the electric field vector Counterclockwise rotation; when the direction of the electric field vector is in the +x direction, a current i1 is generated on the "S"-shaped printed metal strip; when the direction of the electric field vector is in the +y direction, a current i2 opposite to the current direction i1 is generated on the "S"-shaped printed metal strip;
  • i2 has a 90° phase delay compared to i1 , and since the total electrical length of the printed metal strip where the dielectric substrate in the x direction is connected to the dielectric substrate in the y direction is ⁇ /4, i1 has a 90° phase delay compared to i2 , so the phase delays of the two cancel each other out, and equal-amplitude and opposite-direction currents are excited on the "S"-shaped
  • the electric field vector Rotate clockwise; when the electric field vector is in the +y direction, A current i 1 is generated on the "S"-shaped printed metal strip; when the direction of the electric field vector is toward the +x direction, a current i 2 is generated on the "S"-shaped printed metal strip in the opposite direction to the current i 1 , and i 2 has a 90° phase delay compared to i 1.
  • i 2 Since the total electrical length of the printed metal strip at the connection between the dielectric substrate in the x direction and the dielectric substrate in the y direction is ⁇ /4, i 2 has a 90° phase delay compared to i 1 , so i 2 has a total phase delay of 180° compared to i 1. i 2 and i 1 have the same direction, and the currents of the two cancel each other out, and the entire structure exhibits a non-resonant transmission state.
  • the incident electromagnetic wave when the incident electromagnetic wave is a left-hand circularly polarized wave or a right-hand circularly polarized wave, the current situation generated on the first group of "S"-shaped printed metal strips is opposite; among them, when the incident electromagnetic wave is a left-hand circularly polarized wave, the currents on the second group of "S"-shaped printed metal strips are canceled out, and the entire structure exhibits a non-resonant transmission state; when the incident electromagnetic wave is a right-hand circularly polarized wave, equal-amplitude and opposite currents will be excited on the second group of "S"-shaped printed metal strips, and the whole exhibits a wavelength resonance, and the right-hand circularly polarized wave is reflected.
  • the present invention adopts the above technical solution and has the following technical effects:
  • the dual circularly polarized reflectarray antenna based on double "S"-shaped printed metal strips proposed in the present invention can simultaneously reflect left-hand circularly polarized waves and right-hand circularly polarized waves, and realizes the characteristics of independent controllable radiation beams of left-hand circularly polarized waves and right-hand circularly polarized waves under the premise of ensuring high-gain radiation.
  • the reflective unit of the double "S"-shaped printed metal strips proposed in the present invention has a simple structure and excellent performance, and is easy to process and realize.
  • FIG1 is a schematic diagram of the three-dimensional structure of the dual circularly polarized reflectarray antenna of the present invention.
  • FIG. 2 is a schematic diagram of the three-dimensional structure of the double “S”-shaped printed metal strip reflective unit of the present invention.
  • FIG3 is a schematic diagram of the planar structure of the dielectric substrate and the “S”-shaped printed metal strip of the double “S”-shaped printed metal strip reflective unit of the present invention.
  • FIG. 4 is a graph showing a variation trend of the aperture efficiency of the reflectarray antenna with F/D in an embodiment of the present invention.
  • 5 is a graph showing the gain and axial ratio of the reflectarray antenna at the radiation center frequency of 10 GHz as a function of F/D for the left-hand circularly polarized wave and the right-hand circularly polarized wave in an embodiment of the present invention.
  • Figure 6 is the reflection phase required in an embodiment of the present invention, wherein Figure 6 (a) is the reflection phase required for each double "S"-shaped printed metal strip reflection unit of the reflectarray antenna when a left-handed circularly polarized wave is incident, and Figure 6 (b) is the reflection phase required for each double "S"-shaped printed metal strip reflection unit of the reflectarray antenna when a right-handed circularly polarized wave is incident.
  • FIG. 7 is a diagram showing the relationship between the relative position of the first group of "S" shaped printed metal strips on the dielectric substrate and its reflection phase and reflection amplitude at the antenna radiation center frequency of 10 GHz in the double "S" shaped printed metal strip reflection unit in an embodiment of the present invention.
  • FIG. 9 is a graph showing the variation of gain and axial ratio with frequency for left-hand circularly polarized waves and right-hand circularly polarized waves of the reflectarray antenna in the frequency band from 9 GHz to 11 GHz according to an embodiment of the present invention.
  • FIG10 is a far-field radiation pattern of left-hand circularly polarized waves and right-hand circularly polarized waves of the reflectarray antenna at a radiation center frequency of 10 GHz in an embodiment of the present invention.
  • the present invention proposes a dual circularly polarized reflectarray antenna with independently controllable radiation beams.
  • the three-dimensional structure is shown in FIG1, and includes a circularly polarized antenna feed 1 and a dual "S"-shaped printed metal strip reflectarray 2.
  • the circularly polarized antenna feed 1 faces the dual "S"-shaped printed metal strip reflectarray 2 along the -z direction, and is located directly in front of the dual "S"-shaped printed metal strip reflectarray 2, and is located at the phase shift focus of the dual "S"-shaped printed metal strip reflectarray 2, so that the spherical electromagnetic wave radiated by the circularly polarized antenna feed 1 becomes a uniform plane wave after reflection.
  • the distance between the phase center of the circularly polarized antenna feed 1 and the reflection array of the dual "S"-shaped printed metal strip reflectarray 2 is 217 mm.
  • the double “S” type printed metal strip reflective array 2 is composed of 31 ⁇ 31 double “S” type printed metal strip reflective units 3 with the same structure and different relative positions of two groups of "S" type printed metal strips on the dielectric substrate.
  • the double “S” type printed metal strip reflective units 3 are extended periodically along the y axis and then stacked periodically at a certain interval along the x axis, where px is the period size of the double "S” type printed metal strip reflective units 3 arranged in parallel in sequence along the x direction, and py is the period size of the double "S” type printed metal strip reflective units 3 stacked in sequence along the y direction.
  • the three-dimensional structure of the double "S" type printed metal strip reflective unit 3 is shown in FIG2, including two perpendicular orthogonal dielectric substrates and two "symmetrical” printed metal strips arranged on the dielectric substrate.
  • the RO4003C dielectric substrate is selected, with a thickness of 0.406 mm, a relative dielectric constant of 3.55, and a loss tangent of 0.0027.
  • the printed metal strip is made of copper with a thickness of 0.017 mm.
  • the two dielectric substrates of the double "S"-shaped printed metal strip reflector unit 3 are assembled by plugging to form two groups of cascaded "S"-shaped printed metal strips, and the two parts of the "S"-shaped printed metal strips are connected by welding.
  • the unit period size of the double "S" type printed metal strip reflective unit 3 is related to the oblique incidence performance.
  • the smaller the unit period the better the oblique incidence performance.
  • different unit period sizes are simulated.
  • the unit period is larger than 7mm, the reflection oblique incidence performance will deteriorate more severely;
  • the unit period is smaller than 7mm, since the unit period is already relatively small, a smaller unit period will not significantly improve the reflection performance, but under the same aperture size, the number of units will increase. Therefore, 7mm is selected as the unit period size of this example.
  • the planar structure of the double “S” shaped printed metal strip reflector unit 3 is shown in FIG3 .
  • the first group of "S" type printed metal strips 4 and the second group of “S” type printed metal strips 5 in the strip reflector unit 3 have the same size, and both have a total length of l 1 + l 2 + l 3 + l 4 , that is, 1 working center frequency wavelength.
  • p z is the length of the double "S" type printed metal strip reflector unit 3 in the z direction
  • l 1 , l 2 , l 3 , l 4 are the lengths of the "S" type printed metal strips
  • r is the arc of the "S” type printed metal strips
  • w is the width of the "S” type printed metal strips
  • dz and dz 1 are the relative positions of the two groups of "S" type printed metal strips on the dielectric substrate.
  • the first group of "S"-shaped printed metal strips 4 reflects left-handed circularly polarized waves and is located near one end of the circularly polarized antenna feed source 1, that is, the coordinate is dz
  • the second group of "S"-shaped printed metal strips 5 reflects right-handed circularly polarized waves and is located far from the circularly polarized antenna feed source 1, that is, the coordinate is dz 1.
  • the double "S"-shaped printed metal strip reflective array 2 adjusts the reflection phase of left-handed circularly polarized waves and right-handed circularly polarized waves by respectively changing the positions of the first group of "S"-shaped printed metal strips 4 and the second group of "S"-shaped printed metal strips 5 on the dielectric substrate.
  • Step 1 determine the size D of the double "S" type printed metal strip reflective array 2 and the appropriate focal diameter ratio F/D, where F is the distance between the circularly polarized antenna feed 1 and the double "S" type printed metal strip reflective array 2.
  • F is the distance between the circularly polarized antenna feed 1 and the double "S" type printed metal strip reflective array 2.
  • the determination of the F/D value depends on the aperture efficiency, and the main factors affecting the aperture efficiency are the taper efficiency and the overflow efficiency.
  • the specific calculation formula is:
  • ⁇ taper is the taper efficiency
  • ⁇ spillover is the spillover efficiency
  • A is the aperture area
  • P is the Poynting vector of the electromagnetic wave radiated by the circularly polarized antenna feed source, which can be approximately calculated by the cosine function model
  • I represents the excitation received by each array element.
  • the value of F/D is selected to be 1.
  • Step 2 According to the value of F/D in step 1 and the reflection angles -15° and +15° required for the left-handed circularly polarized wave and the right-handed circularly polarized wave, respectively, the reflection phase required by the double "S" type printed metal strip reflection unit 3 when the left-handed circularly polarized wave and the right-handed circularly polarized wave are incident is determined.
  • the specific contents are as follows:
  • i-th double “S” type printed metal strip reflection unit 3 is the reflection phase of the i-th double “S” type printed metal strip reflection unit 3, and the value of i ranges from 1 to 961 (i.e., 31 ⁇ 31);
  • k is the propagation constant in free space;
  • R i is the distance from the circularly polarized antenna feed source 1 to the i-th double “S” type printed metal strip reflection unit 3; is the position vector of the i-th double “S” type printed metal strip reflective unit 3; is the direction in which the antenna radiates the main beam; is a phase constant, indicating that the phase shift value required by the double “S” type printed metal strip reflective array 2 is a relative phase value rather than an absolute phase value.
  • dz and dz1 represent the relative positions of two groups of “S”-shaped printed metal strips on the dielectric substrate.
  • the reflection phase of the left-hand circularly polarized wave and the right-hand circularly polarized wave that can be achieved by each unit is determined based on the above formula: range, will exceed the range
  • the value is folded, minus the 360° phase
  • the horizontal and vertical axes in the figure represent the number of units in the x-direction and the y-direction, and there are 31 ⁇ 31 grids in total.
  • the depth of each grid color represents the different reflection phase values required by the double "S" type printed metal strip reflection unit 3 at that position.
  • Figure 6 (a) represents the reflection phase required by each double "S” type printed metal strip reflection unit 3 when a left-handed circularly polarized wave is incident
  • Figure 6 (b) represents the reflection phase required by each double "S” type printed metal strip reflection unit 3 when a right-handed circularly polarized wave is incident.
  • Step 3 according to the reflection phase required by the double "S” type printed metal strip reflection unit 3 and the relationship between the position of the two groups of "S” type printed metal strips on the dielectric substrate and the reflection phase of the left-handed circularly polarized wave and the right-handed circularly polarized wave, determine the position of the two groups of "S" type printed metal strips of each unit on the dielectric substrate, thereby determining the final structure of the entire double "S" type printed metal strip reflection array 2.
  • Step 4 Place the circularly polarized antenna feed 1 and the double "S"-shaped printed metal strip reflect array 2 according to the positional relationship shown in FIG1 .
  • the distance between the circularly polarized antenna feed 1 and the double "S"-shaped printed metal strip reflect array 2 is determined by F determined in step 1. At this point, the entire dual circularly polarized reflect array antenna is completed.
  • Step 5 Taking one of the double “S”-shaped printed metal strip reflector units 3 as an example, for the first group of “S”-shaped printed metal strips 4, when the incident electromagnetic wave is a left-handed circularly polarized wave, the electric field vector Counterclockwise rotation. When the electric field vector is in the +x direction, a current i 1 is generated on the "S"-shaped printed metal strip. When the electric field vector is in the +y direction, a current i 2 opposite to the current i 1 is generated on the "S"-shaped printed metal strip.
  • i 2 has a 90° phase delay compared to i 1
  • i 1 has a 90° phase delay compared to i 2 , so the phase delays of the two cancel each other out.
  • Equal-amplitude and opposite-direction currents are excited on the "S"-shaped printed metal strip, which exhibits a wavelength resonance as a whole, and the left-handed circularly polarized wave is reflected.
  • the electric field vector Rotate clockwise.
  • a current i 1 is generated on the "S"-shaped printed metal strip;
  • a current i 2 is generated on the "S"-shaped printed metal strip in the opposite direction to the current i 1 , and i 2 has a 90° phase delay compared to i 1.
  • i 2 Since the total electrical length of the printed metal strip at the connection between the dielectric substrate in the x direction and the dielectric substrate in the y direction is ⁇ /4, i 2 has a 90° phase delay compared to i 1 , so i 2 has a total of 180° phase delay compared to i 1 , and i 2 and i 1 have the same direction, the currents cancel each other out, and the entire structure exhibits a non-resonant transmission state.
  • the total electrical length of the metal strip is ⁇ /4, so i2 will have a 90° phase delay compared to i1 , so i2 will have a total phase delay of 180° compared to i1 . Then i1 and i2 have the same direction, the currents cancel each other out, and the entire structure exhibits a non-resonant transmission state.
  • the electric field vector Rotate clockwise.
  • a current i 1 is generated on the "S"-shaped printed metal strip;
  • a current i 2 is generated on the "S"-shaped printed metal strip in the opposite direction to the current i 1 , and i 2 has a 90° phase delay compared to i 1.
  • the total electrical length of the printed metal strip where the dielectric substrate in the x direction is connected to the dielectric substrate in the y direction is ⁇ /4
  • i 1 will also have a 90° phase delay compared to i 2. Therefore, the relative phase delays of the two cancel each other out, and equal-amplitude reverse currents are excited on the "S"-shaped printed metal strip, which exhibits a wavelength resonance as a whole, and the right-handed circularly polarized wave is reflected.
  • FIG7 shows a relationship diagram between the position of the first group of "S"-shaped printed metal strips 4 in the double “S”-shaped printed metal strip reflection unit 3 on the dielectric substrate and the reflection phase of the left-handed circularly polarized wave and the right-handed circularly polarized wave at the antenna radiation center frequency of 10 GHz.
  • the horizontal axis in the figure is the position of the double "S"-shaped printed metal strips on the dielectric substrate, in millimeters (mm), and the vertical axis in the figure is the phase and reflection amplitude, in degrees (deg) and dB, respectively.
  • Fig. 8 shows the relationship between the position of the second group of "S"-shaped printed metal strips 5 on the dielectric substrate and the reflection phase of the left-hand circularly polarized wave and the right-hand circularly polarized wave in the double "S"-shaped printed metal strip reflection unit 3 at the antenna radiation center frequency of 10 GHz.
  • changing dz 1 will change the reflection phase of the right-hand circularly polarized wave, but it has little effect on the reflection phase of the left-hand circularly polarized wave and the reflection amplitude of the left-hand circularly polarized wave and the right-hand circularly polarized wave, so the requirement for the reflection phase of the right-hand circularly polarized wave of each double "S"-shaped printed metal strip reflection unit 3 can be met by changing dz 1 .
  • the two groups of "S"-shaped printed metal strips in the double "S"-shaped printed metal strip reflection unit 3 move forward and backward without interfering with each other.
  • the reflection phase of the double "S"-shaped printed metal strip reflection unit 3 can be uniquely determined by the positions of the two groups of "S"-shaped printed metal strips on the dielectric substrate.
  • Figure 9 shows the curves of gain and axial ratio of the reflectarray antenna for left-hand circularly polarized waves and right-hand circularly polarized waves changing with frequency.
  • the horizontal axis in the figure is frequency, in GHz; the vertical axis is gain and axial ratio, in dB.
  • the reflectarray antenna achieves high gain characteristics of 24.2dB for left-hand circularly polarized waves and 23.5dB for right-hand circularly polarized waves at the antenna radiation center frequency of 10GHz.
  • the range of gain reduction by 1dB is 9.49GHz-10.15GHz and 9.53GHz-10.17GHz, respectively, and the absolute bandwidth is 0.66GHz and 0.64GHz, respectively, and the relative bandwidth is about 6.7% and 6.5%, respectively.
  • the range of 3dB axial ratio is 8.02-10.57GHz and 9.06-10.86GHz, respectively, and the absolute bandwidth is 2.55GHz and 1.8GHz, respectively, and the relative bandwidth is about 27.6% and 18.1%, respectively.
  • Figure 10 shows the normalized far-field radiation pattern of the reflectarray antenna for left-hand circularly polarized waves and right-hand circularly polarized waves at the radiation center frequency.
  • the horizontal axis in the figure is the angle, in degrees.
  • the vertical axis in the figure is the gain, in dB. It can be seen from the figure that this high-gain reflectarray antenna achieves a narrow beam, and the lobe levels at other angles are relatively low.
  • the highest sidelobe level of the left-hand circularly polarized wave is only about -16dB, and the highest sidelobe level of the right-hand circularly polarized wave is only about -13.6dB.
  • the high-gain reflectarray antenna has good cross-polarization isolation, and the cross-polarization of the left-hand circularly polarized wave and the right-hand circularly polarized wave are both lower than -20dB.
  • the antenna proposed in the present invention achieves a good high-gain radiation effect, can simultaneously reflect left-hand circularly polarized waves and right-hand circularly polarized waves, and realizes the independent controllable characteristics of left-hand circularly polarized wave beams and right-hand circularly polarized wave radiation beams under the premise of ensuring high-gain radiation.
  • this dual circularly polarized reflectarray antenna based on double "S"-shaped printed metal strips is easy to manufacture and has excellent performance, and has good application prospects in the field of radar communication applications.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
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Abstract

本发明公开了一种双圆极化反射阵天线及其辐射波束独立控制方法，该天线包括圆极化天线馈源和双"S"型印刷金属条带反射阵列，所述圆极化天线馈源朝向双"S"型印刷金属条带反射阵列，所述圆极化天线馈源位于双"S"型印刷金属条带反射阵列的移相焦点；圆极化天线馈源发射球面电磁波，双"S"型印刷金属条带反射阵列接收球面电磁波并反射为平面波。本发明提供的双圆极化反射阵天线，可同时反射左旋圆极化波和右旋圆极化波，在保证高增益辐射的前提下，实现了左旋圆极化波波束和右旋圆极化波辐射波束独立可控的特性。

Description

双圆极化反射阵天线及其辐射波束独立控制方法 技术领域
本发明属于雷达通信技术领域，尤其涉及双圆极化反射阵天线及其辐射波束独立控制方法。
背景技术
随着现代卫星通信技术的快速发展，具有多波束有效载荷的高通量卫星得到了广泛的发展。设计、开发和发射此类卫星的关键挑战之一是处理任务所需的大量天线，这类卫星通常使用四色频率/极化复用方案，因此设计在同一频率下的双圆极化反射阵天线可以有效缩减卫星所需天线的个数。
天线是现代武器装备、雷达探测系统中的重要组成部分，并且往往要求天线具有高增益的特点。其中，反射阵天线由喇叭馈源和反射阵列组成，具有高增益、无需复杂馈电网络的优点，具有巨大的研究价值。其工作机理是：具有移相功能的反射阵列将来自馈源的球面波转化为平面波向外辐射出去，即可实现具有高增益的辐射性能。
现有的双圆极化反射阵天线，常采用线-圆极化转换器和线极化反射阵天线组合实现，如M.-A.Joyal,R.El Hani,M.Riel,Y.Demers and J.-J.Laurin,"A Reflectarray-Based Dual-Surface Reflector Working in Circular Polarization,"in IEEE Transactions on Antennas and Propagation,vol.63,no.4,pp.1306-1313,April 2015.中，将输入的圆极化波转化为水平线极化波和垂直线极化波，通过一层反射水平线极化波、透射垂直线极化波的反射阵列和一块抛物面反射器，分别对水平线极化波和垂直线极化波进行反射，再将反射的两种线极化波，通过线-圆极化转换器转换为圆极化波输出，但是为了实现对左旋圆极化波和右旋圆极化波的不同角度的输出，各个组件间需要搭建不同的角度，对加工实现有很大的难度。中国专利一种双频双圆极化折叠反射阵天线”(申请号：CN 202111341584.5，公开号：CN 114069256A)提出了一种双频双圆极化折叠反射阵天线，包括主反射镜、副透射镜、支撑结构和馈源，主反射镜包括中心镂空的第一介质基板，该介质基板的上表面印制有周期性排布的方环形金属贴片，下表面印制有金属地板；副透射镜包括上下层叠的第二介质基板和第三介质基板，第二介质基板的下表面印制有带漏波缝隙的金属地板，第二介质基板的上表面和第三介质基板的下表面均印制有两种不同规格的圆形金属贴片，并通过穿过漏波缝隙的金属化过孔连接。这种方法的缺点是需要多层结构、结构复杂，且不能在同一频率下同时反射左旋圆极化波和右旋圆极化波。
此外，S.Mener,R.Gillard,R.Sauleau,A.Bellion and P.Potier,"Dual Circularly Polarized Reflectarray With Independent Control of Polarizations,"in IEEE Transactions on Antennas and Propagation.中采用圆极化选择表面和半波片反射单元，通过第一功能层的圆极化选择作用，实现两种圆极化的分离和独立控制，但该方法的单元难以小型化，斜入射性能差，同时同样由多层平面结构组成，单元剖面高，结构复杂，对加工实现的要求同样较高。因此，需要研究一种辐射波束独立可控的双圆极化反射阵天线。
发明内容
本发明所要解决的技术问题是：提供辐射波束独立可控的双圆极化反射阵天线，通过两块介质基板与两组“S”型印刷金属条带构成反射单元，再组成反射阵列，形成双圆极化反射阵天线，结构简单，且在保证天线良好的辐射性能的前提下，同时反射左旋圆极化波和右旋圆极化波，并可分别独立控制其辐射波束。
本发明为解决上述技术问题采用以下技术方案：
双圆极化反射阵天线，包括用于发射球面电磁波的圆极化天线馈源以及用于接收球面电磁波并将其反射为平面波的双“S”型印刷金属条带反射阵列；所述双“S”型印刷金属条带反射阵列由若干双“S”型印刷金属条带反射单元阵列排布构成。
所述圆极化天线馈源沿-z方向朝向双“S”型印刷金属条带反射阵列，并位于双“S”型印刷金属条带反射阵列的移相焦点。
进一步的，所述双“S”型印刷金属条带反射单元包括两块垂直正交的介质基板，每块介质基板上均设置有两条呈对称形式的半S型印刷金属条带；两块介质基板通过插接形式组装，形成两组级联的“S”型印刷金属条带。
进一步的，所述双“S”型印刷金属条带反射单元中，第一组“S”型印刷金属条带与第二组“S”型印刷金属条带尺寸相同，为工作中心频率波长。
所述第一组“S”型印刷金属条带反射左旋圆极化波，位于靠近圆极化天线馈源一端，第二组“S”型印刷金属条带反射右旋圆极化波，位于远离圆极化天线馈源一端。
进一步的，每个双“S”型印刷金属条带反射单元中两组“S”型印刷金属条带在介质基板上所在位置均不相同，以满足左旋圆极化波和右旋圆极化波所需要的不同补偿相位。具体位置的计算内容为：
步骤1、计算反射相位，具体公式为：
其中，是第i个双“S”型印刷金属条带反射单元的反射相位，i的取值从1至M×N；k是自由空间中的传播常数；Ri是圆极化天线馈源1到第i个双“S”型印刷金属条带反射单元的距离；是第i个双“S”型印刷金属条带反射单元的位置矢量；是天线辐射主波束的方向；是一个相位常数，表示双“S”型印刷金属条带反射阵列所需的移相值。
步骤2、“S”型印刷金属条带在介质基板上所在位置与反射相位之间的关系为：

其中，dz和dz1表示两组“S”型印刷金属条带在介质基板上的相对位置。
进一步的，将所述双“S”型印刷金属条带反射单元进行阵列排布，具体排布方式包括：沿x方向依次平行排布若干双“S”型印刷金属条带反射单元，沿y方向依次堆叠若干双“S”型印刷金属条带反射单元。
进一步的，所述“S”型印刷金属条带在x方向平行排布的相邻双“S”型印刷金属条带反射单元之间的“S”型印刷金属条带之间的距离记为第一距离。
所述“S”型印刷金属条带在y方向堆叠的相邻双“S”型印刷金属条带反射单元之间的“S”型印刷金属条带之间的距离记为第二距离。
所述第一距离等于第二距离。
进一步的，本发明还提出了双圆极化反射阵天线的辐射波束独立控制方法，针对第一组“S”型印刷金属条带，当入射电磁波为左旋圆极化波时，电场矢量逆时针旋转；电场矢量方向朝+x方向时，在“S”型印刷金属条带上产生电流i1；电场矢量方向朝+y方向时，在“S”型印刷金属条带上产生与电流方向i1相反的电流i2；i2相比i1会有90°的相位延迟，由于x方向上的介质基板与y方向上的介质基板相连接处的印刷金属条带总电长度为λ/4，则i1相比i2会有90°的相位延迟，因此两者相位延迟相互抵消，在“S”型印刷金属条带上激励起等幅反向的电流，整体表现出一个波长谐振，左旋圆极化波被反射；其中λ是工作中心频率的波长。
当入射电磁波为右旋圆极化波时，电场矢量顺时针旋转；电场矢量方向朝+y方向时， 在“S”型印刷金属条带上产生电流i1；电场矢量方向朝+x方向时，在“S”型印刷金属条带上产生与电流方向i1相反的电流i2，i2相比i1会有90°的相位延迟，由于x方向上的介质基板与y方向上的介质基板相连接处的印刷金属条带总电长度为λ/4，则i2相比i1会有90°的相位延迟，因此i2相比i1一共会有180°的相位延迟，i2和i1方向相同，两者电流互相抵消，整个结构表现为非谐振的透射状态。
进一步的，针对第二组“S”型印刷金属条带，当入射电磁波为左旋圆极化波或右旋圆极化波时，与在第一组“S”型印刷金属条带上产生的电流情况相反；其中，当入射电磁波为左旋圆极化波时，第二组“S”型印刷金属条带上的电流被相互抵消，整个结构表现为非谐振的透射状态；当入射电磁波为右旋圆极化波时，第二组“S”型印刷金属条带上会激励起等幅反向的电流，整体表现出一个波长谐振，右旋圆极化波被反射。
本发明采用以上技术方案与现有技术相比，具有以下技术效果：
本发明提出的基于双“S”型印刷金属条带的双圆极化反射阵天线，可以同时反射左旋圆极化波和右旋圆极化波，在保证高增益辐射的前提下实现了左旋圆极化波和右旋圆极化波辐射波束独立可控的特性。同时，本发明提出的双“S”型印刷金属条带的反射单元结构简单性能优秀，便于加工和实现。
附图说明
图1是本发明双圆极化反射阵天线的三维结构示意图。
图2是本发明双“S”型印刷金属条带反射单元的三维结构示意图。
图3是本发明双“S”型印刷金属条带反射单元的介质基板及“S”型印刷金属条带平面结构示意图。
图4是本发明实施例中反射阵天线的口径效率随F/D的变化趋势图。
图5是本发明实施例中反射阵天线左旋圆极化波和右旋圆极化波在辐射中心频率10GHz处增益与轴比随F/D变化图。
图6是本发明实施例中所需要的反射相位，其中图6的(a)是反射阵天线每个双“S”型印刷金属条带反射单元在左旋圆极化波入射时所需要的反射相位，图6的(b)是反射阵天线每个双“S”型印刷金属条带反射单元右旋圆极化波入射时所需要的反射相位。
图7是本发明实施例中双“S”型印刷金属条带反射单元在天线辐射中心频率10GHz处，第一组“S”型印刷金属条带在介质基板上的相对位置与其反射相位与反射幅度的关系图。
图8是本发明实施例中双“S”型印刷金属条带反射单元在天线辐射中心频率10GHz处，第二组“S”型印刷金属条带在介质基板上的相对位置与其反射相位与反射幅度的关系图。
图9是本发明实施例中反射阵天线左旋圆极化波与右旋圆极化波在9GHz至11GHz的频带范围内增益与轴比随频率变化图。
图10是本发明实施例中反射阵天线在辐射中心频率10GHz处左旋圆极化波与右旋圆极化波的远场方向图。
具体实施方式
下面基于附图对本发明作进一步描述。以下实施例仅用于更加清楚地说明本发明的技术方案，而不能以此来限制本发明的保护范围。
下面结合附图对本发明做进一步详细说明。
本发明提出了辐射波束独立可控的双圆极化反射阵天线，三维结构如图1所示，包括圆极化天线馈源1和双“S”型印刷金属条带反射阵列2。圆极化天线馈源1沿-z方向朝向双“S”型印刷金属条带反射阵列2，并位于双“S”型印刷金属条带反射阵列2的正前方，处在双“S”型印刷金属条带反射阵列2的移相焦点，使得圆极化天线馈源1辐射出的球面电磁波经反射后变为均匀平面波。圆极化天线馈源1的相位中心与双“S”型印刷金属条带反射阵列2的反射阵面的距离为217mm。
双“S”型印刷金属条带反射阵列2由31×31个结构相同、两组“S”型印刷金属条带在介质基板上的相对位置不同的双“S”型印刷金属条带反射单元3周期排布构成，将双“S”型印刷金属条带反射单元3沿y轴周期延拓，再沿x轴以一定间隔周期堆叠，其中px为双“S”型印刷金属条带反射单元3沿x方向依次平行排布的周期大小，py为双“S”型印刷金属条带反射单元3沿y方向依次堆叠的周期大小。双“S”型印刷金属条带反射单元3的三维结构如图2所示，包括两块垂直正交的介质基板和设置于介质基板上的两条呈“对称”形式的印刷金属条带。选用的是RO4003C介质基板，厚度为0.406mm，相对介电常数为3.55，损耗角正切为0.0027。印刷金属条带选用铜，厚度为0.017mm。双“S”型印刷金属条带反射单元3的两块介质基板通过插接形式组装，形成了两组级联的“S”型印刷金属条带，“S”型印刷金属条带的两部分通过焊接连接。
双“S”型印刷金属条带反射单元3的单元周期大小与斜入射性能有关，单元周期越小，斜入射性能越好。本实例中仿真了不同单元周期大小的情况，当单元周期比7mm大时反射斜入射性能会恶化的比较厉害；当单元周期比7mm小时，由于单元周期已经比较小了，再小对反射性能并没有太大优化，但是在相同口径大小的情况下，会增加单元数。因此选取的7mm为本实例的单元周期大小。
双“S”型印刷金属条带反射单元3的平面结构如图3所示，每一个双“S”型印刷金属 条带反射单元3中的第一组“S”型印刷金属条带4与第二组“S”型印刷金属条带5尺寸相同，均为l1+l2+l3+l4的总长度，即为1个工作中心频率波长。pz为双“S”型印刷金属条带反射单元3在z方向的长度，l1、l2、l3、l4为“S”型印刷金属条带的长度，r为“S”型印刷金属条带的弧度，w为“S”型印刷金属条带的宽度，dz和dz1为两组“S”型印刷金属条带在介质基板上的相对位置。
本实例中的物理参数分别为：px＝7mm，py＝7mm，pz＝50mm，l1＝2.625mm，l2＝3.41mm，l3＝4.5mm，l4＝1.9mm，r＝1mm，w＝0.15mm。
所述第一组“S”型印刷金属条带4反射左旋圆极化波，位于靠近圆极化天线馈源1一端，即坐标为dz，第二组“S”型印刷金属条带5反射右旋圆极化波，位于远离圆极化天线馈源1一端，即坐标为dz1。双“S”型印刷金属条带反射阵列2通过分别改变第一组“S”型印刷金属条带4和第二组“S”型印刷金属条带5在介质基板上的所在位置，来实现左旋圆极化波和右旋圆极化波反射相位的调节。为了使双“S”型印刷金属条带反射阵列2受圆极化天线馈源1照射后二次辐射/散射的能量具有高增益的特点，每个双“S”型印刷金属条带反射单元3中两组“S”型印刷金属条带在介质基板上的位置均不相同。
工作原理为：
步骤1、确定双“S”型印刷金属条带反射阵列2的大小D和合适的焦径比F/D，其中F为圆极化天线馈源1与双“S”型印刷金属条带反射阵列2之间的距离。F/D值的确定，取决于口径效率，而影响口径效率的主要因素是锥削效率和溢出效率，具体计算公式为：

其中，ηtaper为锥削效率；ηspillover为溢出效率；A为口径面面积；P是圆极化天线馈源辐射电磁波的坡印廷矢量，可由余弦函数模型近似计算；I表示每个阵元受到的激励。
基于上式可以得出反射阵天线的口径效率随F/D的变化趋势图，如图4所示，随着焦径 比增加，圆极化天线馈源会逐渐远离反射阵面，这使溢出阵面辐射能量更多，同时照射在阵面上的能量也会更加均匀，溢出效率随焦径比增加而降低，而锥削效率随焦径比增加而上升，理论上，最佳口径效率对应的F/D约为0.9。但是通过如图5所示的仿真图，验证不同F/D情况下反射阵天线的性能，图中的横坐标为频率，单位为GHz；纵坐标为增益和轴比，单位是dB。分别展示了左旋圆极化波与右旋圆极化波在辐射中心频率10GHz处增益与轴比随F/D变化关系，可以发现F/D＝1时，性能最优，是因为当F/D＝0.9时，圆极化天线馈源到阵面边缘的入射角度变大，而大角度斜入射会影响双“S”型印刷金属条带反射单元3的响应，最终反映到反射阵天线的性能上就是增益下降与轴比恶化。
因此本实施例中，选定F/D的大小为1。
步骤2、根据步骤1中F/D的值和左、右旋圆极化波分别需要的反射角度-15°、+15°，确定双“S”型印刷金属条带反射单元3在左旋圆极化波和右旋圆极化波入射时所需要的反射相位，具体内容为：
(1)计算反射相位，具体公式为：
其中，是第i个双“S”型印刷金属条带反射单元3的反射相位，i的取值从1至961(即31×31)；k是自由空间中的传播常数；Ri是圆极化天线馈源1到第i个双“S”型印刷金属条带反射单元3的距离；是第i个双“S”型印刷金属条带反射单元3的位置矢量；是天线辐射主波束的方向；是一个相位常数，表示双“S”型印刷金属条带反射阵列2所需的移相值是相对相位值而不是绝对相位值。
(2)“S”型印刷金属条带在介质基板上所在位置与反射相位之间的关系为：

其中，dz和dz1表示两组“S”型印刷金属条带在介质基板上的相对位置。
由于介质基板在z方向的长度pz为50mm，基于上述公式确定每个单元可以实现的左旋圆极化波与右旋圆极化波反射相位的范围，将超出范围的值进行折叠，减去360°相位 值。如图6所示，图中的横坐标与纵坐标表示x方向与y方向的单元数，一共有31×31格，每一格颜色的深浅代表处在那个位置的双“S”型印刷金属条带反射单元3所需要的不同的反射相位值。图6的(a)代表左旋圆极化波入射时，每个双“S”型印刷金属条带反射单元3所需要的反射相位，图6的(b)代表右旋圆极化波入射时，每个双“S”型印刷金属条带反射单元3所需要的反射相位。
步骤3、根据双“S”型印刷金属条带反射单元3所需的反射相位和两组“S”型印刷金属条带在介质基板上的所在位置与左旋圆极化波和右旋圆极化波反射相位的关系，确定每个单元两组“S”型印刷金属条带在介质基板上的所在位置，从而确定整个双“S”型印刷金属条带反射阵列2的最终结构。
步骤4、将圆极化天线馈源1和双“S”型印刷金属条带反射阵列2按照图1所示的位置关系进行放置，圆极化天线馈源1和双“S”型印刷金属条带反射阵列2的距离由步骤1所确定的F决定。此时整个双圆极化反射阵天线搭建完成。
步骤5、以其中一个双“S”型印刷金属条带反射单元3为例，针对第一组“S”型印刷金属条带4，当入射电磁波为左旋圆极化波时，电场矢量逆时针旋转。电场矢量方向朝+x方向时，在“S”型印刷金属条带上产生电流i1，电场矢量方向朝+y方向时，在“S”型印刷金属条带上产生与电流方向i1相反的电流i2。虽然i2相比i1会有90°的相位延迟，但是由于x方向上的介质基板与y方向上的介质基板相连接处的印刷金属条带总电长度为λ/4，则i1相比i2会有90°的相位延迟，因此两者相位延迟相互抵消。在“S”型印刷金属条带上激励起等幅反向的电流，整体表现出一个波长谐振，左旋圆极化波被反射。
当入射电磁波为右旋圆极化波时，电场矢量顺时针旋转。电场矢量方向朝+y方向时，在“S”型印刷金属条带上产生电流i1；电场矢量方向朝+x方向时，在“S”型印刷金属条带上产生与电流方向i1相反的电流i2，i2相比i1会有90°的相位延迟，由于x方向上的介质基板与y方向上的介质基板相连接处的印刷金属条带总电长度为λ/4，则i2相比i1会有90°的相位延迟，因此i2相比i1一共会有180°的相位延迟，则i2和i1方向相同，电流互相抵消，整个结构表现为非谐振的透射状态。
同理，针对第二组“S”型印刷金属条带5，当入射电磁波为左旋圆极化波时，电场矢量逆时针旋转。电场矢量方向朝+x方向时，在“S”型印刷金属条带上产生电流i1，电场矢量方向朝+y方向时，在“S”型印刷金属条带上产生与电流方向i1相反的电流i2，i2相比i1会有90°的相位延迟。同时由于x方向上的介质基板与y方向上的介质基板相连接处的印刷 金属条带总电长度为λ/4，则i2相比i1还会有90°的相位延迟，所以i2相比i1一共会有180°的相位延迟，则i1和i2方向相同，电流互相抵消，整个结构表现为非谐振的透射状态。
当入射电磁波为右旋圆极化波时，电场矢量顺时针旋转。电场矢量方向朝+y方向时，在“S”型印刷金属条带上产生电流i1；电场矢量方向朝+x方向时，在“S”型印刷金属条带上产生与电流方向i1相反的电流i2，i2相比i1会有90°的相位延迟，由于x方向上的介质基板与y方向上的介质基板相连接处的印刷金属条带总电长度为λ/4，则i1相比i2也会有90°的相位延迟，因此两者相对的相位延迟相互抵消，在“S”型印刷金属条带上激励起等幅反向的电流，整体表现出一个波长谐振，右旋圆极化波被反射。
图7表示在天线辐射中心频率10GHz处，双“S”型印刷金属条带反射单元3中第一组“S”型印刷金属条带4在介质基板上的所在位置与左旋圆极化波和右旋圆极化波反射相位的关系图。图中横坐标为双“S”型印刷金属条带在介质基板上的所在位置，单位为毫米(mm)，图中纵坐标为相位和反射幅度，单位分别为度(deg)和dB。从图中可以看出，改变dz，会改变左旋圆极化波的反射相位，但是对右旋圆极化波的反射相位、左旋圆极化波和右旋圆极化波的反射幅度基本没影响，所以可以通过改变dz，来满足对每个双“S”型印刷金属条带反射单元3左旋圆极化波反射相位的要求。
图8表示在天线辐射中心频率10GHz处，双“S”型印刷金属条带反射单元3中第二组“S”型印刷金属条带5在介质基板上的所在位置与左旋圆极化波和右旋圆极化波反射相位的关系图。从图中可以看出，改变dz1，会改变右旋圆极化波的反射相位，但是对左旋圆极化波的反射相位、左旋圆极化波和右旋圆极化波的反射幅度基本没影响，所以可以通过改变dz1，来满足对每个双“S”型印刷金属条带反射单元3右旋圆极化波反射相位的要求。
双“S”型印刷金属条带反射单元3中两组“S”型印刷金属条带前后移动基本互不干扰，双“S”型印刷金属条带反射单元3的反射相位可由两组“S”型印刷金属条带在介质基板上的所在位置唯一确定。
图9给出了反射阵天线左旋圆极化波和右旋圆极化波的增益与轴比随频率的变化曲线。图中的横坐标为频率，单位为GHz；纵坐标为增益和轴比，单位是dB。反射阵天线在天线辐射中心频率10GHz实现了左旋圆极化波24.2dB和右旋圆极化波23.5dB的高增益特性，增益降低1dB的范围分别为9.49GHz-10.15GHz和9.53GHz-10.17GHz，绝对带宽分别为0.66GHz和0.64GHz，相对带宽分别约为6.7％和6.5％，3dB轴比的范围分别为8.02-10.57GHz和9.06-10.86GHz，绝对带宽分别为2.55GHz和1.8GHz，相对带宽分别约为27.6％和18.1％。
图10给出了反射阵天线在辐射中心频率左旋圆极化波和右旋圆极化波的归一化远场方向图，图中的横坐标为角度，单位为度deg。图中纵坐标为增益，单位是dB。由图中可以看出，此高增益反射阵天线实现了较窄的波束，且在其他角度的波瓣电平都比较低，左旋圆极化波最高的副瓣电平仅约为-16dB，右旋圆极化波最高的副瓣电平仅约为-13.6dB。同时，该高增益反射阵天线具有良好的交叉极化隔离度，左旋圆极化波和右旋圆极化波的交叉极化均低于-20dB。
综合以上的实验结果可以看出，本发明提出的天线实现了较好的高增益辐射效果，可同时反射左旋圆极化波和右旋圆极化波，在保证高增益辐射的前提下实现了左旋圆极化波波束和右旋圆极化波辐射波束独立可控的特性。除此之外，此基于双“S”型印刷金属条带的双圆极化反射阵天线制作简便，性能优，在雷达通信应用领域具有较好的应用前景。
以上所述仅是本发明的优选实施方式，应当指出，对于本技术领域的普通技术人员来说，在不脱离本发明技术原理的前提下，还可以做出若干改进和变形，这些改进和变形也应视为本发明的保护范围。

Claims (8)

  1. 双圆极化反射阵天线，包括用于发射球面电磁波的圆极化天线馈源(1)，以及用于接收球面电磁波并将其反射为平面波的双“S”型印刷金属条带反射阵列(2)；其特征在于，所述双“S”型印刷金属条带反射阵列(2)由若干双“S”型印刷金属条带反射单元(3)阵列排布构成；
    所述圆极化天线馈源(1)沿-z方向朝向双“S”型印刷金属条带反射阵列(2)，并位于双“S”型印刷金属条带反射阵列(2)的移相焦点。
  2. 根据权利要求1所述的双圆极化反射阵天线，其特征在于，所述双“S”型印刷金属条带反射单元(3)包括两块垂直正交的介质基板，每块介质基板上均设置有两条呈对称形式的半S型印刷金属条带；两块介质基板通过插接形式组装，形成两组级联的“S”型印刷金属条带。
  3. 根据权利要求1所述的双圆极化反射阵天线，其特征在于，所述双“S”型印刷金属条带反射单元(3)中，第一组“S”型印刷金属条带(4)与第二组“S”型印刷金属条带(5)尺寸相同，为工作中心频率波长；
    所述第一组“S”型印刷金属条带(4)反射左旋圆极化波，位于靠近圆极化天线馈源一端，第二组“S”型印刷金属条带(5)反射右旋圆极化波，位于远离圆极化天线馈源一端。
  4. 根据权利要求3所述的双圆极化反射阵天线，其特征在于，每个双“S”型印刷金属条带反射单元(3)中两组“S”型印刷金属条带在介质基板上的位置均不相同，具体位置的计算步骤为：
    步骤S1、计算反射相位，具体公式为：
    其中，是第i个双“S”型印刷金属条带反射单元(3)的反射相位，i的取值从1至M×N；k是自由空间中的传播常数；Ri是圆极化天线馈源1到第i个双“S”型印刷金属条带反射单元(3)的距离；是第i个双“S”型印刷金属条带反射单元(3)的位置矢量；是天线辐射主波束的方向；是一个相位常数，表示双“S”型印刷金属条带反射阵列(2)所需的移相值；
    步骤S2、“S”型印刷金属条带在介质基板上所在位置与反射相位之间的关系为：

    其中，dz和dz1表示两组“S”型印刷金属条带在介质基板上的相对位置。
  5. 根据权利要求1所述的双圆极化反射阵天线，其特征在于，将所述双“S”型印刷金属条带反射单元(3)进行阵列排布，具体排布方式包括：沿x方向依次平行排布若干双“S”型印刷金属条带反射单元(3)，沿y方向依次堆叠若干双“S”型印刷金属条带反射单元(3)。
  6. 根据权利要求5所述的双圆极化反射阵天线，其特征在于，所述“S”型印刷金属条带在x方向平行排布的相邻双“S”型印刷金属条带反射单元(3)之间的“S”型印刷金属条带之间的距离记为第一距离；
    所述“S”型印刷金属条带在y方向堆叠的相邻双“S”型印刷金属条带反射单元(3)之间的“S”型印刷金属条带之间的距离记为第二距离；
    所述第一距离等于第二距离。
  7. 双圆极化反射阵天线的辐射波束独立控制方法，其特征在于，针对第一组“S”型印刷金属条带(4)，当入射电磁波为左旋圆极化波时，电场矢量逆时针旋转；电场矢量方向朝+x方向时，在“S”型印刷金属条带上产生电流i1；电场矢量方向朝+y方向时，在“S”型印刷金属条带上产生与电流方向i1相反的电流i2，两者相位延迟相互抵消，在“S”型印刷金属条带上激励起等幅反向的电流，整体表现出一个波长谐振，左旋圆极化波被反射；其中λ是工作中心频率的波长；
    当入射电磁波为右旋圆极化波时，电场矢量顺时针旋转；电场矢量方向朝+y方向时，在“S”型印刷金属条带上产生电流i1；电场矢量方向朝+x方向时，在“S”型印刷金属条带上产生与电流方向i1相反的电流i2，两者电流互相抵消，整个结构表现为非谐振的透射状态。
  8. 根据权利要求7所述的双圆极化反射阵天线的辐射波束独立控制方法，其特征在于，针对第二组“S”型印刷金属条带(5)，当入射电磁波为左旋圆极化波或右旋圆极化波时，与在第一组“S”型印刷金属条带(4)上产生的电流情况相反；其中
    当入射电磁波为左旋圆极化波时，第二组“S”型印刷金属条带(5)上的电流被相互抵消，整个结构表现为非谐振的透射状态；
    当入射电磁波为右旋圆极化波时，第二组“S”型印刷金属条带(5)上会激励起等幅反向的电流，整体表现出一个波长谐振，右旋圆极化波被反射。
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