WO2023279581A1 - 基于注入锁定倍频的相干微波光子雷达探测方法及系统 - Google Patents

基于注入锁定倍频的相干微波光子雷达探测方法及系统 Download PDF

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WO2023279581A1
WO2023279581A1 PCT/CN2021/126522 CN2021126522W WO2023279581A1 WO 2023279581 A1 WO2023279581 A1 WO 2023279581A1 CN 2021126522 W CN2021126522 W CN 2021126522W WO 2023279581 A1 WO2023279581 A1 WO 2023279581A1
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signal
optical
radar
sideband
frequency
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PCT/CN2021/126522
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English (en)
French (fr)
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郭清水
尹坤
吉晨
王继厚
应小俊
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之江实验室
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/35—Details of non-pulse systems
    • G01S7/352—Receivers
    • G01S7/354—Extracting wanted echo-signals
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/03—Details of HF subsystems specially adapted therefor, e.g. common to transmitter and receiver
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S17/00—Systems using the reflection or reradiation of electromagnetic waves other than radio waves, e.g. lidar systems
    • G01S17/02—Systems using the reflection of electromagnetic waves other than radio waves
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/0209—Systems with very large relative bandwidth, i.e. larger than 10 %, e.g. baseband, pulse, carrier-free, ultrawideband
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/06—Systems determining position data of a target
    • G01S13/08—Systems for measuring distance only
    • G01S13/32—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated
    • G01S13/34—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated using transmission of continuous, frequency-modulated waves while heterodyning the received signal, or a signal derived therefrom, with a locally-generated signal related to the contemporaneously transmitted signal
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/35—Details of non-pulse systems
    • G01S7/352—Receivers
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/48—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S17/00
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/60—Receivers
    • H04B10/61—Coherent receivers
    • H04B10/615—Arrangements affecting the optical part of the receiver

Definitions

  • the invention relates to a radar detection method, in particular to a microwave photon radar detection method and system based on optical injection locking frequency multiplication and coherent reception.
  • Real-time high-precision radar is widely used in military and civilian fields, and multi-functional full-spectrum detection is one of the main directions of the development of modern radar technology. In order to cover the wide-area spectrum space, this requires the radar working band to be flexible and adjustable, and the signal can be processed and analyzed with high precision in real time.
  • the current wideband radar signal generation scheme based on photon frequency multiplication technology has the following problems: 1) The frequency multiplication factor of optical frequency multiplication based on a special modulator is limited and cannot be flexibly adjusted; 2) The photoelectric control link is complex and there are strong The spurious interference signal generated by the non-ideal sideband beat frequency; 3) The signal generation method limits the radar signal reception scheme. Most of the radar signal reception schemes are difficult to achieve the reception of broadband target echo signals through coherent reception.
  • the technical problem to be solved by the present invention is: to overcome the deficiencies of the existing technology, based on the optical injection locking mechanism, use the distributed feedback laser to filter and amplify the high-order sweep frequency sidebands respectively, and obtain the broadband radar transmission signal with flexible and adjustable frequency multiplication factor ; And based on the coherent receiving technology, the real-time quadrature de-slope of the broadband echo signal is realized.
  • the system is flexible and adjustable, and has excellent anti-interference performance.
  • a baseband chirp signal with a frequency of f LFM to modulate the optical carrier f C output by the main laser through an electro-optical modulator, to obtain a modulated optical signal comprising high-order modulation sidebands f C ⁇ nf LFM , wherein n is a positive integer;
  • the modulated optical signal is divided into two paths and then injected into two slave lasers for high-order sideband injection locking.
  • the two slave lasers output the first amplified locked sideband f C ⁇ Mf LFM and the second amplified locked sideband f C ⁇ Nf LFM Optical signal, where M and N are positive integers; one of the locked sideband optical signals is selected and divided into two channels, one channel is combined with another amplified locked sideband optical signal to form a radar detection optical signal, and the other channel is used as a pair of received optical signals
  • the radar echo signal is received to obtain the radar receiving light signal;
  • the radar detection light signal is divided into two paths, one of which is obtained through photoelectric conversion to obtain the frequency-multiplied radar emission signal (M+N)f LFM , and the frequency-multiplied radar emission signal encounters the target Reflection occurs to obtain the radar echo signal; another radar detection optical signal is used as a reference optical signal and the radar receiving optical signal to achieve coherent reception of the radar echo signal, and a complex intermediate frequency signal carrying target information is obtained, and the intermediate frequency signal is processed , to extract the detection target information.
  • the slave laser is a distributed feedback laser capable of filtering and amplifying modulation sidebands close to its working frequency.
  • the free operating frequency of the slave laser needs to meet certain conditions, among which the free operating frequency f SL1 of the first slave laser whose frequency is close to the sideband f C ⁇ Mf LFM needs to meet:
  • f d1 is the mode spacing of the first slave laser
  • I 11 is the optical injection power of the first slave laser
  • I 10 is the output power of the first slave laser
  • ⁇ 1 is the linewidth enhancement factor related to the first slave laser
  • the second slave laser free operating frequency f SL2 with a frequency close to the sideband f C ⁇ Nf LFM needs to satisfy:
  • the parameter has the same definition as the parameter in the above-mentioned constraint formula of the operating frequency of the first slave laser, and is a relevant parameter of the second slave laser.
  • f d2 is the mode spacing of the second slave laser
  • I 12 is the optical injection power of the second slave laser
  • I 02 is the output power of the second slave laser
  • ⁇ 2 is the linewidth enhancement associated with the second slave laser factor.
  • the different sidebands of the modulated optical signal can be selectively locked in and amplified, thereby realizing the difference between the radar transmitted signal and the baseband chirp signal.
  • Multiplication factor M+N (M and N are positive integers).
  • a coherent microwave photonic radar detection system based on injection-locked frequency doubling including:
  • a main laser for generating an optical carrier signal f C ;
  • the first electro-optic modulator is used to modulate the baseband chirp signal to the optical carrier signal to obtain a modulated optical signal comprising high-order modulation sidebands f C ⁇ nf LFM (n is a positive integer);
  • the first optical coupler is used to divide the modulated optical signal into two paths;
  • the two slave lasers are respectively used to receive the two modulated optical signals output by the first optical coupler, and filter and amplify the specific sideband of the modulated optical signal to obtain the first amplified locked sideband signal f C ⁇ Mf LFM and the second amplified Lock sideband signal f C ⁇ Nf LFM , M and N are positive integers;
  • the third optocoupler is used to divide the second amplified locked sideband signal f C ⁇ Nf LFM into two paths, and send them to the second electro-optic modulator and the second optocoupler respectively;
  • the second optical coupler is used to combine the first amplified locked sideband signal f C ⁇ Mf LFM with a second amplified locked sideband signal f C ⁇ Nf LFM output by the third optical coupler into a radar detection light signal, Then it is divided into two paths, which are respectively sent to the 90-degree optocoupler and photodetector;
  • the photoelectric detector is used for photoelectric conversion of the radar detection light signal to obtain the frequency-doubled radar emission signal
  • the power amplifier and the transmitting antenna are used for power amplification and signal transmission of the frequency multiplication radar transmission signal
  • the receiving antenna and low noise amplifier are used to receive the radar echo signal and perform low noise amplification
  • the second electro-optical modulator is used to modulate the radar echo signal to the output of the third optical coupler as an amplified locking sideband signal of the received optical signal to obtain the radar received optical signal and send it to the 90-degree optical coupler;
  • the 90-degree optical coupler is used to introduce a 90-degree phase difference between the input radar detection optical signal and the radar receiving optical signal in the optical domain, and output four composite optical signals;
  • Two balanced photodetectors are used to photoelectrically detect the four optical signals output by the 90-degree optical coupler to obtain two orthogonal intermediate frequency signals carrying target information;
  • the signal acquisition and processing module is used for analog-to-digital conversion of two orthogonal intermediate frequency signals, and radar digital signal processing to extract target information.
  • first electro-optic modulator and the second electro-optic modulator are Mach-Zehnder modulators, intensity modulators or phase modulators, respectively.
  • control unit is also included, and the control unit sends a control signal to make the first slave laser and the second slave laser work in the working state of setting and locking the high-order sideband respectively, so as to obtain the set frequency multiplication factor M+N( M and N are positive integers).
  • two optical circulators are also included, wherein the first port of the first optical circulator is connected to the output end of the first optical coupler, the second port is connected to the input end of the first slave laser, and the third port is connected to the first
  • the input terminals of the two optical couplers are connected, and are used to inject the modulated optical signal output by the first optical coupler into the first slave laser, and send the amplified locked sideband signal output by the first slave laser to the second optical coupler;
  • the first port of the two optical circulators is connected to the other output end of the first optical coupler, the second port is connected to the input end of the second slave laser, and the third port is connected to the input end of the third optical coupler for inject another modulated optical signal output by the first optical coupler into the second slave laser, and send the amplified locked sideband signal output by the second slave laser to the third optical coupler.
  • the signal generation part of the present invention filters and amplifies different high-order sidebands of the modulated optical signal based on optical injection locking, and can realize the generation of broadband radar detection signals with different frequency multiplication factors, and the frequency multiplication factor can be adjusted by adjusting the working parameters of the laser Realize flexible adjustment, so that the radar system can flexibly switch between different working bands.
  • the signal receiving part of the present invention uses an amplified and locked sideband signal as the optical carrier to realize the reception of the radar echo signal, and combines the optical reference signal to realize real-time quadrature de-FM processing of the broadband radar echo signal in the photoelectric domain, which can effectively Suppress noise and image frequency interference signals, and avoid signal performance degradation caused by electrical domain amplitude/phase consistency problems.
  • the high-order sidebands of the modulated optical signal inherit the advantages of high linearity of the baseband linear frequency sweep signal, and the phase relationship between different sidebands is fixed. After filtering and amplifying the different sidebands from the laser It still inherits the characteristics of the injected signal, so that the linearity and signal-to-noise ratio of the frequency-doubling radar detection signal can be guaranteed.
  • Fig. 1 is a schematic diagram of the principle of the microwave photonic radar system of the present invention
  • Fig. 2 is the signal frequency spectrum and the signal schematic diagram that the corresponding node place produces in the microwave photon radar system shown in Fig. 1;
  • A corresponds to the spectrum distribution of the modulated optical signal
  • B corresponds to the frequency distribution of the first slave laser 1 and its output amplified locked sideband signal
  • C corresponds to the second slave laser 2’s operating frequency and its output amplified locked sideband Band signal spectrum distribution
  • D corresponds to the spectrum distribution of two amplified and locked sideband optical signals combined into one radar detection optical signal
  • E corresponds to the spectrum distribution of a part of the radar receiving optical signal
  • F corresponds to the radar detection of the input balance detector Optical signal and the spectrum diagram of the optical signal received by the radar
  • G corresponds to the spectrum in the complex form of the intermediate frequency signal.
  • the idea of the present invention is to generate broadband, high-frequency, tunable chirp radar transmission signals based on optical injection locking different high-order sideband signals, and realize coherent reception of broadband echo signals through photon coherent reception methods.
  • the working parameters of the radar in this solution are flexible and adjustable, the signal processing is real-time and efficient, and the ability to resist strays is strong.
  • a coherent microwave photon radar detection system based on injection-locked frequency multiplication of the present invention includes: 1 main laser, 1 signal source, 2 electro-optic modulators, 2 optical circulators, 2 Slave laser, 3 optocouplers (OC), 1 control unit, 1 high frequency photodetector (PD), 1 90 degree optocoupler, 2 balanced photodetectors (BPD), 1 electric power amplifier (EA), 1 low-noise amplifier (LNA), 1 transmitting antenna (TA), 1 receiving antenna (RA), and 1 signal acquisition and processing module.
  • the electro-optic modulator can use various modulator types, preferably, the intensity modulator scheme is selected in this embodiment.
  • the main laser output frequency is an optical carrier signal of f C
  • the baseband chirp signal passes through the first
  • An electro-optical modulator performs intensity modulation on the optical carrier signal to obtain a modulated optical signal containing high-order modulation sidebands f C ⁇ nf LFM (n is a positive integer), as shown in A of Figure 2, where f 0 is the baseband chirp
  • the starting frequency of the signal, k is the frequency modulation slope, and T is the signal period.
  • the modulated optical signal is divided into two parts by the first optical coupler, and sent to the first port 1 of the first optical circulator and the second optical circulator respectively (the input of the first port 1 of the first optical circulator is output from the second port 2 , the second port 2 input is output from the third port 3); the first optical port of the laser is connected with the second port 2 port of the first optical circulator, and its free operating frequency f SL1 and a modulation sideband of the modulated optical signal Closer, assuming here that it is the -4th order sideband, then the first slave laser performs lock-in filtering and amplification on the -4th order sideband of the modulated optical signal input to it through the first optical circulator, and the first slave laser outputs the first amplified locked sideband With f C -4f LFM signal, its spectrum diagram is shown in B of Fig.
  • the optical port of the second slave laser is connected to the second port 2 of the second optical circulator, and its free operating frequency f SL2 is close to another modulation sideband of the modulated optical signal, which is assumed to be +4th order sideband here , then the second slave laser performs lock-in filtering and amplification on the modulated optical signal + 4th-order sideband input to it through the second optical circulator, and the second slave laser outputs the second amplified lock-in sideband f C +4f LFM signal, its spectrum diagram As shown in C of Figure 2.
  • Select one of the locked sideband optical signals (take the second amplified locked sideband as an example) to be divided into two paths through the third optical coupler, select one of the locked sideband optical signals as the received optical signal to receive the radar echo signal, and the other
  • One channel and the first amplified locking sideband optical signal are combined into one radar detection optical signal through the second optical coupler, and its frequency spectrum is shown in Figure 2D, and the time domain signal can be expressed as:
  • a 1 and A 2 are the electric field amplitudes of the two locked sidebands, respectively.
  • the signal is divided into two parts, one of them is sent to a 90-degree optical coupler as a reference optical signal, and the other is converted by a photoelectric detector to obtain a frequency-doubled radar transmission signal, and its instantaneous frequency is 8f LFM .
  • EA electric power amplifier
  • TA transmitting antenna
  • RA receiving antenna
  • the delay of the radar echo signal relative to the radar emission is ⁇ .
  • the amplified radar echo signal is modulated by the second electro-optical modulator to another second amplified locking sideband optical signal, so as to realize the optical domain reception of the radar echo signal.
  • the negative first-order signal of the second amplified and locked-in sideband optical signal is close to the first amplified and locked-in sideband optical signal, and there is an intermediate frequency signal related to the target information, so the following analysis only needs to focus on the negative first-order signal.
  • the spectral distribution of the optical signal including the second amplified locking sideband and its negative first-order modulation sideband is shown in E of Figure 2, and the time domain signal can be expressed as:
  • a 3 and A 4 are the electric field amplitudes of the two sidebands, respectively.
  • the signal is sent to a 90-degree optical coupler and a reference optical signal to achieve coherent reception in the optical domain phase shift, wherein the spectrum diagram of the radar detection optical signal input to the balanced detector and the radar received optical signal is shown in Figure 2 F,
  • the 90-degree optocoupler output signal can be expressed as:
  • S I+ (t), S I- (t), S Q+ (t), and S Q- (t) are the four optical signals output by the 90-degree optical coupler, and the four optical signals output by the 90-degree optical coupler
  • the signals are respectively sent to two balanced photodetectors to complete the photoelectric conversion, ignoring the parasitic phase, the obtained intermediate frequency electrical signal can be expressed as:
  • A is the amplitude of the intermediate frequency signal. After the analog-to-digital conversion of the intermediate frequency signal, the target distance, velocity, scattering characteristics and other information can be obtained based on the radar signal processing algorithm. Its spectrum is shown in G in Figure 2.
  • This solution introduces optical injection locking technology in the transmitting part of the radar system.
  • it can filter and amplify different high-order modulation sideband signals, and realize the generation of broadband radar signals with flexible and adjustable frequency multiplication factors; and based on photon coherence
  • the receiving scheme on the basis of ensuring that the system can realize frequency multiplication, can coherently receive broadband receiving signals in real time to obtain complex intermediate frequency signals.
  • the real number IF signal it not only has one more dimension of information, but also has a stronger ability to resist image frequency interference.
  • the overall signal-to-noise ratio of the receiver can also be greatly improved.

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  • Remote Sensing (AREA)
  • Physics & Mathematics (AREA)
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Abstract

一种基于注入锁定倍频的相干微波光子雷达探测方法及系统，该方法利用基带信号调制光载波生成包含多个高阶边带的调制光信号，调制光信号分成两路分别注入两个从激光器进行高阶边带注入锁定获得两个锁定边带光信号；选择其中一个锁定边带光信号分为两路，一路作为接收光信号对雷达回波接收得到雷达接收光信号，另一路与另一个锁定边带光信号合为一起后分为两路，一路经光电转换后获得倍频雷达发射信号；另一路与雷达接收光信号实现雷达回波信号的相干接收，得到中频信号，提取可获得探测目标信息。该方法通过光子注入锁定技术及光子相干接收技术，可实现倍频可重构雷达信号产生及相干接收，雷达系统参数灵活可调，抗干扰能力强。

Description

基于注入锁定倍频的相干微波光子雷达探测方法及系统 技术领域
本发明涉及一种雷达探测方法，尤其涉及一种基于光注入锁定倍频与相干接收的微波光子雷达探测方法及系统。
背景技术
实时高精度雷达广泛应用于军事、民用领域，多功能全频谱探测是现代雷达技术的发展的主要方向之一。为了覆盖广域频谱空间，这就需要雷达工作波段灵活可调，信号可实时高精度处理分析。受限于目前电子技术瓶颈限制，射频放大、匹配、传输链路在承载宽带信号的产生、采样、处理等功能时，存在潜在的幅度/相位非线性效应，限制了雷达向高频宽带发展(参见[S.Kim,N.Myung,"Wideband linear frequency modulated waveform compensation using system predistortion and phase coefficients extraction method,"IEEE Microwave and Wireless Components Letters,vol.17,no.11,pp.808-810,2007.])。得益于微波光子技术的快速发展，微波信号的光域产生、传输、处理，如光子混频、光子采样、光子真延时等为克服传统雷达电子瓶颈问题，改善提高技术性能，提供了新的技术支撑，成为下一代雷达的关键技术(参见[J.Mckinney,"Photonics illuminates the future of radar,"Nature,vol.507,no.7492,pp.310-312,2014.])。如基于光子倍频技术的宽带雷达探测信号产生及基于光子混频技术的宽带雷达回波信号实时接收处理等技术已在新型雷达接收技术中使用(参见[F.Zhang,Q.Guo,Z.Wang,etc,"Photonics-based broadband radar for high-resolution and real-time inverse synthetic aperture imaging,"Optics Express,vol.25,no.14,pp.16274-16281,2017.])。但目前基于光子倍频技术实现宽带雷达信号产生方案存在以下问题：1)基于特殊调制器实现光倍频的倍频因子有限且不能灵活可调；2)光电控制链路复杂，且存在较强非理想边带拍频生成的寄生干扰信号；3)信号产生方式限制了雷达信号接收方案大多难以通过相干接收实现宽带目标回波信号的接收。
发明内容
本发明所要解决的技术问题在于：克服现有技术不足，基于光注入锁定机理，利用分布反馈式激光器对高阶扫频边带分别进行滤波放大，得到倍频因子灵活可调的宽带雷达发射信号；并基于相干接收技术，实现宽带回波信号的实时正交去斜。系统灵活可调，抗干扰性能 优异。
本发明具体采用以下技术方案解决上述技术问题：
利用频率为f LFM的基带线性调频信号通过电光调制器对主激光器输出的光载波f C进行调制，获得包含高阶调制边带f C±nf LFM的调制光信号，其中，n为正整数；调制光信号分成两路后分别注入两个从激光器进行高阶边带注入锁定，两个从激光器分别输出第一放大锁定边带f C±Mf LFM与第二放大锁定边带f C±Nf LFM光信号，其中，M与N为正整数；选择其中一个锁定边带光信号分为两路，一路与另一放大锁定边带光信号合为一路雷达探测光信号，另一路作为接收光信号对雷达回波信号接收得到雷达接收光信号；所述雷达探测光信号分为两路，其中一路经光电转换后获得倍频雷达发射信号(M+N)f LFM，倍频雷达发射信号遇到目标发生反射得到所述雷达回波信号；另一路雷达探测光信号作为参考光信号与雷达接收光信号实现雷达回波信号的相干接收，得到携带目标信息的复中频信号，对所述中频信号进行处理，提取获得探测目标信息。
优选地，所述从激光器为分布反馈式激光器，可对靠近它工作频率的调制边带进行滤波放大作用。从激光器的自由工作频率需满足一定条件，其中频率靠近边带f C±Mf LFM的第一从激光器自由工作频率f SL1需满足：
Figure PCTCN2021126522-appb-000001
其中，f d1为第一从激光器的模式间隔，I 11为第一从激光器的光注入功率，I 10为第一从激光器的输出功率，α 1为与第一从激光器相关的线宽增强因子；而频率靠近边带f C±Nf LFM的第二从激光器自由工作频率f SL2需满足：
Figure PCTCN2021126522-appb-000002
其中参数与上述关于第一从激光器的工作频率约束公式中参数有相同的定义，为第二从激光器的相关参数。具体地，f d2为第二从激光器的模式间隔，I 12为第二从激光器的光注入功率，I 02为第二从激光器的输出功率，α 2为与第二从激光器相关的线宽增强因子。
进一步地，通过控制两个从激光器的自由工作波长、光注入功率，输出功率等参数，可以对调制光信号的不同边带进行选择性锁定放大，从而实现雷达发射信号相对基带线性调频信号不同的倍频因子M+N(M与N为正整数)。
根据相同的发明思路还可以得到以下技术方案：
一种基于注入锁定倍频的相干微波光子雷达探测系统，包括：
主激光器，用于生成光载波信号f C；
信号源，用于生成频率为f LFM的基带线性调频信号；
第一电光调制器，用于将基带线性调频信号对光载波信号进行调制获得包含高阶调制边带f C±nf LFM(n为正整数)的调制光信号；
第一光耦合器，用于将调制光信号分为两路；
两个从激光器，分别用于接收第一光耦合器输出的两路调制光信号，将调制光信号特定边带进行滤波锁定放大得到第一放大锁定边带信号f C±Mf LFM与第二放大锁定边带信号f C±Nf LFM，M与N为正整数；
第三光耦合器，用于将第二放大锁定边带信号f C±Nf LFM分为两路，并分别送给第二电光调制器与第二光耦合器；
第二光耦合器，用于将第一放大锁定边带信号f C±Mf LFM与第三光耦合器输出的一路第二放大锁定边带信号f C±Nf LFM合为一路雷达探测光信号，然后分为两路，分别送给90度光耦合器与光电探测器；
光电探测器，用于对雷达探测光信号进行光电转换，得到倍频雷达发射信号；
功率放大器及发射天线，用于对倍频雷达发射信号进行功率放大以及信号发射；
接收天线及低噪声放大器，用于接收雷达回波信号并进行低噪声放大；
第二电光调制器，用于将雷达回波信号对第三光耦合器输出的一路作为接收光信号的放大锁定边带信号进行调制，得到雷达接收光信号，并送给90度光耦合器；
90度光耦合器，用于对输入的雷达探测光信号与雷达接收光信号在光域引入90度相位差，输出四路复合光信号；
两个平衡光电探测器，用于对90度光耦合器输出的四路光信号分别进行光电探测，得到携带目标信息的两路正交中频信号；
信号采集处理模块，用于两路正交中频信号进行模数转换，并进行雷达数字信号处理，提取出目标信息。
进一步地，所述第一电光调制器、第二电光调制器分别为马赫-曾德尔调制器、强度调制器或相位调制器。
进一步地，还包括控制单元，所述控制单元发出控制信号使第一从激光器与第二从激光器分别工作在设定锁定高阶边带的工作状态，得到设定的倍频因子M+N(M与N为正整数)。
进一步地，还包括两个光环形器，其中第一光环形器的第一端口与第一光耦合器的输出端连接，第二端口与第一从激光器的输入端连接，第三端口与第二光耦合器的输入端连接，用于将第一光耦合器输出的调制光信号注入第一从激光器，并将第一从激光器输出的放大锁定边带信号送给第二光耦合器；第二光环形器的第一端口与第一光耦合器的另一输出端连接，第二端口与第二从激光器的输入端连接，第三端口与第三光耦合器的输入端连接，用于将第 一光耦合器输出的另一路调制光信号注入第二从激光器，并将第二从激光器输出的放大锁定边带信号送给第三光耦合器。
相比现有技术，本发明技术方案具有以下有益效果：
1)本发明信号产生部分，基于光注入锁定分别滤波放大调制光信号的不同高阶边带，可实现不同倍频因子的宽带雷达探测信号产生，且倍频因子可通过调节从激光器的工作参数实现灵活调节，从而使雷达系统在不同工作波段间灵活转换。
2)本发明信号接收部分，以一个放大锁定边带信号为光载波对雷达回波信号实现接收，结合光参考信号，在光电域实现宽带雷达回波信号的实时正交去调频处理，可有效抑制噪声及镜频干扰信号，并且可以避免电域幅度/相位一致性问题带来的信号性能恶化问题。
3)本发明信号产生部分，调制光信号的高阶边带继承了基带线性扫频信号的高线性度等优点，且不同边带之间相位关系固定，从激光器对不同边带进行滤波放大后依然继承了注入信号的特性，从而可以保证倍频雷达探测信号的线性度、信噪比等性能。
附图说明
图1为本发明微波光子雷达系统原理示意图；
图2为图1所示微波光子雷达系统中对应节点处产生的信号频谱及信号示意图；
其中，A对应为调制光信号频谱分布，B对应为第一从激光器1工作频率及其输出的放大锁定边带信号频谱分布，C对应为第二从激光器2工作频率及其输出的放大锁定边带信号频谱分布，D对应为两个放大锁定边带光信号合为一路雷达探测光信号的频谱分布，E对应为雷达接收光信号部分区域的频谱分布，F对应为输入平衡探测器的雷达探测光信号与雷达接收光信号的光谱图，G对应为中频信号复数形式的频谱。
具体实施方式
针对现有技术的不足，本发明的思路是基于光注入锁定不同高阶边带信号产生宽带、高频段、可调谐的线性调频雷达发射信号，通过光子相干接收方法实现宽带回波信号相干接收。本方案雷达工作参数灵活可调，信号处理实时高效，抗杂散能力强。
本发明的一种基于注入锁定倍频的相干微波光子雷达探测系统，如图1所示，包括：1个主激光器、1个信号源、2个电光调制器、2个光环形器、2个从激光器、3个光耦合器(OC)、1个控制单元、1个高频光电探测器(PD)、1个90度光耦合器、2个平衡光电探测器(BPD)、1个电功率放大器(EA)、1个低噪声放大器(LNA)、1个发射天线(TA)、1个接收天线(RA)、1个信号采集处理模块。
需要说明的是，所述电光调制器可采用多种调制器类型，优选地，本实施例选择强度调 制器方案。
本发明的相干微波光子雷达探测系统，首先主激光器输出频率为f C的光载波信号，信号源产生的频率为f LFM＝f 0+kt(0≤t≤T)的基带线性调频信号通过第一电光调制器对光载波信号进行强度调制，获得包含高阶调制边带f C±nf LFM(n为正整数)的调制光信号，如图2的A所示，其中f 0为基带线性调频信号的起始频率，k为调频斜率，T为信号周期。调制光信号通过第一光耦合器分为两部分，分别送入第一光环形器与第二光环形器的第一端口1(第一光环形器第一端口1输入从第二端口2输出，第二端口2输入从第三端口3输出)；第一从激光器的光端口与第一光环形器的第二端口2端口连接，其自由工作频率f SL1与调制光信号的一个调制边带靠近，此处假设为-4阶边带，则第一从激光器对通过第一光环形器输入其的调制光信号-4阶边带进行锁定滤波放大，第一从激光器输出第一放大锁定边带f C-4f LFM信号，其频谱图如图2的B所示。同理，第二从激光器的光端口与第二光环形器的第二端口2连接，其自由工作频率f SL2与调制光信号的另一个调制边带靠近，此处假设为+4阶边带，则第二从激光器对通过第二光环形器输入其的调制光信号+4阶边带进行锁定滤波放大，第二从激光器输出第二放大锁定边带f C+4f LFM信号，其频谱图如图2的C所示。
选择其中一个锁定边带光信号(以第二放大锁定边带为例)通过第三光耦合器分为两路，选择其中一路锁定边带光信号作为接收光信号对雷达回波信号接收，另一路与第一放大锁定边带光信号通过第二光耦合器合为一路雷达探测光信号，其频谱图如图2的D所示，时域信号可以表示为：
S Tr(t)＝A 1exp[j2π(f C-4(f 0+kt))t]+A 2exp[j2π(f C+4(f 0+kt))t] (0≤t≤T)        (1)
其中，A 1与A 2分别为两个锁定边带的电场幅度。将该信号分为两部分后，其中一路作为参考光信号送入90度光耦合器，另一路经光电探测器光电转换后可获得倍频雷达发射信号，其瞬时频率为8f LFM，将该信号通过电功率放大器(EA)放大后经发射天线(TA)发射。目标回波信号经接收天线(RA)接收后，送入低噪声放大器进行放大，设雷达回波信号相对雷达发射的延时为τ。放大后的雷达回波信号通过第二电光调制器对另一路第二放大锁定边带光信号调制，实现雷达回波信号的光域接收。考虑到只有第二放大锁定边带光信号的负一阶信号与第一放大锁定边带光信号靠近，相差一个与目标信息相关的中频信号，因此以下主要分析负一阶信号即可。包含第二放大锁定边带及其负一阶调制边带的光信号频谱分布如图2的E所示，时域信号可以表示为：
S Re(t)＝A 3exp[j2π(f C-4(f 0+k(t-τ)))(t-τ)]+A 4exp[j2π(f C+4(f 0+kt))t] (0≤t≤T)     (2)
A 3与A 4分别为两个边带的电场幅度。将该信号送入90度光耦合器与参考光信号实现相干接收的光域移相，其中，输入平衡探测器的雷达探测光信号与雷达接收光信号的光谱图如图2 的F所示，90度光耦合器输出信号可以表示为：
Figure PCTCN2021126522-appb-000003
S I+(t)、S I-(t)、S Q+(t)、S Q-(t)分别为90度光耦合器输出的四路光信号，将90度光耦合器输出的四路光信号分别送入两个平衡光电探测器完成光电转换，忽略寄生相位，得到的中频电信号可以表示为：
Figure PCTCN2021126522-appb-000004
即携带目标信息中频信号的两个正交分量S I(t)、S Q(t)，其中φ为中频信号的相位信息，对应信号复数形式为：
S IF(t)＝S I(t)+jS Q(t)＝Aexp[j2πkτt+jφ] (0≤t≤T)      (5)
A为中频信号的幅度，将该中频信号模数转换后，基于雷达信号处理算法即可得到目标距离、速度、散射特性等信息，其频谱如图2的G所示。
本方案在雷达系统发射部分引入光注入锁定技术，通过改变被注入激光器的波长等参数可滤波放大不同高阶调制边带信号，实现倍频因子灵活可调的宽带雷达信号产生；并基于光子相干接收方案，在保证系统可实现倍频工作能力的基础上，可对宽带接收信号实时相干接收，得到复数中频信号。相比实数中频信号不仅多一个维度的信息，且具有更强的抵抗镜频干扰的能力。接收机信噪比整体也可大大提升。
最后，需要注意的是，以上列举的仅是本发明的具体实施例。本发明不限于以上实施例，还可以有很多变形。本领域的普通技术人员能从本发明公开的内容中直接导出或联想到的所有变形，均应认为是本发明的保护范围。

Claims (7)

  1. 一种基于注入锁定倍频的相干微波光子雷达探测方法，其特征在于，该方法具体为：
    利用频率为f LFM的基带线性调频信号通过电光调制器对主激光器输出的光载波f C进行调制，获得包含高阶调制边带f C±nf LFM的调制光信号，其中，n为正整数；调制光信号分成两路后分别注入两个从激光器进行高阶边带注入锁定，两个从激光器分别输出第一放大锁定边带f C±Mf LFM与第二放大锁定边带f C±Nf LFM光信号，其中，M与N为正整数；选择其中一个锁定边带光信号分为两路，一路与另一放大锁定边带光信号合为一路雷达探测光信号，另一路作为接收光信号对雷达回波信号接收得到雷达接收光信号；所述雷达探测光信号分为两路，其中一路经光电转换后获得倍频雷达发射信号(M+N)f LFM，倍频雷达发射信号遇到目标发生反射得到所述雷达回波信号；另一路雷达探测光信号作为参考光信号与雷达接收光信号实现雷达回波信号的相干接收，得到携带目标信息的复中频信号，对所述中频信号进行处理，提取获得探测目标信息。
  2. 如权利要求1所述的方法，其特征在于，所述从激光器为分布反馈式激光器，其中频率靠近边带f C±Mf LFM的第一从激光器自由工作频率f SL1需满足：
    Figure PCTCN2021126522-appb-100001
    其中，f d1为第一从激光器的模式间隔，I 11为第一从激光器的光注入功率，I 01为第一从激光器的输出功率，α 1为与第一从激光器相关的线宽增强因子；频率靠近边带f C±Nf LFM的第二从激光器自由工作频率f SL2需满足：
    Figure PCTCN2021126522-appb-100002
    f d2为第二从激光器的模式间隔，I 12为第二从激光器的光注入功率，I 02为第二从激光器的输出功率，α 2为与第二从激光器相关的线宽增强因子。
  3. 如权利要求1所述的方法，其特征在于，通过控制两个从激光器的自由工作波长、光注入功率和输出功率，对调制光信号的不同边带进行选择性锁定放大，从而实现雷达发射信号相对基带线性调频信号不同的倍频因子M+N。
  4. 一种基于注入锁定倍频的相干微波光子雷达探测系统，其特征在于，包括：
    主激光器，用于生成光载波信号f C；
    信号源，用于生成频率为f LFM的基带线性调频信号；
    第一电光调制器，用于将基带线性调频信号对光载波信号进行调制获得包含高阶调制边带f C±nf LFM的调制光信号，其中，n为正整数；
    第一光耦合器，用于将调制光信号分为两路；
    两个从激光器，分别用于接收第一光耦合器输出的两路调制光信号，将调制光信号特定边带进行滤波锁定放大得到第一放大锁定边带信号f C±Mf LFM与第二放大锁定边带信号f C±Nf LFM，M与N为正整数；
    第三光耦合器，用于将第二放大锁定边带信号f C±Nf LFM分为两路，并分别送给第二电光调制器与第二光耦合器；
    第二光耦合器，用于将第一放大锁定边带信号f C±Mf LFM与第三光耦合器输出的一路第二放大锁定边带信号f C±Nf LFM合为一路雷达探测光信号，然后分为两路，分别送给90度光耦合器与光电探测器；
    光电探测器，用于对雷达探测光信号进行光电转换，得到倍频雷达发射信号；
    功率放大器及发射天线，用于对倍频雷达发射信号进行功率放大以及信号发射；
    接收天线及低噪声放大器，用于接收雷达回波信号并进行低噪声放大；
    第二电光调制器，用于将雷达回波信号对第三光耦合器输出的一路作为接收光信号的放大锁定边带信号进行调制，得到雷达接收光信号，并送给90度光耦合器；
    90度光耦合器，用于对输入的雷达探测光信号与雷达接收光信号在光域引入90度相位差，输出四路复合光信号；
    两个平衡光电探测器，用于对90度光耦合器输出的四路光信号分别进行光电探测，得到携带目标信息的两路正交中频信号；
    信号采集处理模块，用于两路正交中频信号进行模数转换，并进行雷达数字信号处理，提取出目标信息。
  5. 根据权利要求4所述的系统，其特征在于，所述从激光器为分布反馈式激光器；所述第一电光调制器、第二电光调制器分别为马赫-曾德尔调制器、强度调制器或相位调制器。
  6. 根据权利要求4所述的系统，其特征在于，还包括控制单元，所述控制单元发出控制信号使第一从激光器与第二从激光器分别工作在设定锁定高阶边带的工作状态，得到设定的倍频因子M+N，M与N为正整数。
  7. 根据权利要求4所述的系统，其特征在于，还包括两个光环形器，其中第一光环形器的第一端口与第一光耦合器的输出端连接，第二端口与第一从激光器的输入端连接，第三端口与第二光耦合器的输入端连接，用于将第一光耦合器输出的调制光信号注入第一从激光器，并将第一从激光器输出的放大锁定边带信号送给第二光耦合器；第二光环形器的第一端口与第一光耦合器的另一输出端连接，第二端口与第二从激光器的输入端连接，第三端口与第三光耦合器的输入端连接，用于将第一光耦合器输出的另一路调制光信号注入第二从激光器，并 将第二从激光器输出的放大锁定边带信号送给第三光耦合器。
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