WO2023005739A1 - Antenna and communication device - Google Patents

Abstract

The present application belong to the technical field of communications. Disclosed are an antenna and an electronic device. The antenna comprises a first radiation structure, a second radiation structure and a switch. The first radiation structure comprises an inverted-F structure and a circuit board, wherein the circuit board is electrically connected to the inverted-F structure by means of a radio-frequency signal port. The second radiation structure comprises a dipole, and the second radiation structure is electrically connected to the first radiation structure by means of a first transmission line. The switch is electrically connected to the first transmission line and the first radiation structure, respectively. When the switch is in a first state, the inverted-F structure is used for exciting, by means of a radio-frequency signal that has been transmitted to the inverted-F structure, the circuit board to radiate electromagnetic waves in a first plane. When the switch is in a second state, the first transmission line is used for transmitting the radio-frequency signal in the inverted-F structure to the second radiation structure, so as to excite the dipole to radiate electromagnetic wave in a second plane. The antenna provided in the present application has a relatively high radiation efficiency.

Description

Antennas and Communications Equipment

This application claims the priority of a Chinese patent application with an application date of July 30, 2021, an application number of 202110875166.8, and an application title of "antenna and communication equipment", the entire contents of which are incorporated in this application by reference.

technical field

The present application relates to the technical field of communications, and in particular to an antenna and a communications device.

Background technique

Communication devices such as wireless routers and optical network terminals (ONT) include antennas, which can radiate electromagnetic waves to realize the communication functions of the communication devices.

Currently, an antenna in a communication device includes: a ground plate, two parallel transmission lines, and a dipole formed by two radiating arms. The two transmission lines are connected to the two radiating arms in a one-to-one correspondence, one of the two transmission lines is used for connecting with the radio frequency signal source, and the other transmission line is used for grounding. Wherein, a PIN diode is provided at the connection between each radiation arm and the corresponding transmission line, and a PIN diode is provided on the transmission line used for grounding among the two transmission lines. When all the PIN diodes in the antenna are in the conduction state, the antenna radiates electromagnetic waves in the vertical plane under the excitation of the radio frequency signal fed by the radio frequency signal source. When all the PIN diodes in the antenna are in the disconnected state, the antenna radiates electromagnetic waves in the horizontal plane under the excitation of the radio frequency signal fed by the radio frequency signal source. However, the radiation efficiency of this antenna is low.

Contents of the invention

The present application provides an antenna and a communication device. The technical scheme of the application is as follows:

In a first aspect, an antenna is provided, and the antenna includes a first radiating structure, a second radiating structure, and a switch. The first radiating structure includes an inverted-F structure and a circuit board, and the circuit board is electrically connected to the inverted-F structure through a radio frequency signal port. The second radiating structure includes a dipole, and the second radiating structure is electrically connected to the first radiating structure through a first transmission line. The switches are respectively electrically connected to the first transmission line and the first radiation structure. When the switch is in the first state, the inverted-F structure is used to excite the circuit board to radiate electromagnetic waves on the first plane through the radio frequency signal transmitted to the inverted-F structure. When the switch is in the second state, the first transmission line is used to transmit the radio frequency signal in the inverted F structure to the second radiation structure, and the dipole is excited to radiate electromagnetic waves on the second plane.

The antenna provided by this application has two radiation modes, which are the first radiation mode in which the first radiation structure (specifically the circuit board in the first radiation structure) radiates electromagnetic waves in the first plane, and the second radiation structure (specifically the circuit board in the first radiation structure) The dipole in the second radiation structure) radiates the second radiation mode of the electromagnetic wave in the second plane. The switch can control the antenna to be in the first radiation mode or the second radiation mode, thereby controlling the antenna to radiate electromagnetic waves on the first plane or the second plane.

The technical solution provided by this application can control the antenna to alternately radiate electromagnetic waves on the first plane and the second plane through the switch. Since the antenna can radiate electromagnetic waves on the first plane and can also radiate electromagnetic waves on the second plane, the electromagnetic waves radiated by the The beam can realize beam reconfiguration, so that the beam coverage of the antenna can be adjusted according to the home environment, the location of the station (STA), etc., and the antenna can be applied to communication scenarios in multi-storey houses. The antenna has high radiation efficiency while realizing beam reconfiguration.

Optionally, the inverted-F structure includes a second transmission line and two matching components, the two matching components are arranged on both sides of the second transmission line, and the two matching components are respectively electrically connected to the second transmission line. The electrically connecting the circuit board to the inverted F structure through the radio frequency signal port includes: electrically connecting the circuit board to the second transmission line through the radio frequency signal port.

Optionally, the second transmission line includes a first feeder and a second feeder, and the first feeder and the second feeder are located in two parallel planes. The two matching components disposed on both sides of the second transmission line include: the two matching components disposed on both sides of the first power feeding part. The electrically connecting the circuit board to the second transmission line through the radio frequency signal port includes: electrically connecting the circuit board to the first power feeding part and the second power feeding part through the radio frequency signal port.

Optionally, the matching component includes a first matching stub and a second matching stub, one end of the first matching stub is electrically connected to the middle of the second matching stub, and the other end of the first matching stub is grounded. The electrical connection of the two matching components with the second transmission line includes: electrically connecting one end of the second matching branch of each matching component with the first power feeding part.

Optionally, the two matching components are approximately symmetrical with respect to the first power feeding part. For example, the difference in the distances between the first matching stubs of the two matching components and the first power feeder is smaller than the first difference threshold, and the difference in the lengths of the second matching stubs of the two matching components is smaller than the second difference Value threshold, the projected length of the distance between the second matching branch of the two matching components and the connection position of the first power feeder in the first direction is less than the first distance threshold, the first direction and the length direction of the first transmission line parallel.

Optionally, the length range of the first matching stub is (0, λ/4), where λ is the working wavelength of the electromagnetic wave radiated by the antenna.

In the technical solution provided by the present application, the matching component can not only be used to construct the inverted F structure, but also can be used to adjust the impedance of the antenna so that the return loss of the antenna is smaller than the preset loss, thereby matching the antenna impedance. The two matching components are roughly symmetrical with respect to the first feeding part, and the length range of the first matching stub is (0, λ/4), so the two matching components can better achieve impedance matching of the antenna.

Optionally, the first transmission line includes a third feeder and a fourth feeder, and the third feeder and the fourth feeder are located in two parallel planes. The switch being electrically connected to the first transmission line and the first radiation structure respectively includes: the switch being electrically connected to the third feeding part and the inverted-F structure respectively.

Optionally, the electrically connecting the switch to the third power feeding part and the inverted-F structure respectively includes: there is a gap between the third power feeding part and the inverted-F structure, and the switch is connected across the gap.

In an example, there is a gap between the third power feeding part and the first power feeding part, and the switch is connected across the gap between the third power feeding part and the first power feeding part. Wherein, the width of the slit is 0.5 mm˜1.0 mm (millimeter).

Optionally, the number of switches is one. Since there is an insertion loss when the switch is turned on, the insertion loss easily affects the radiation efficiency of the antenna. If the insertion loss in the antenna is large, the antenna may not meet the insertion loss requirement of a wireless-fidelity (WiFi) device. The antenna provided by the present application only includes one switch, and the number of switches in the antenna is small, so the insertion loss in the antenna is small, and the insertion loss has little influence on the radiation efficiency of the antenna, which helps to ensure the radiation efficiency of the antenna. Moreover, since the antenna only includes one switch, the antenna can meet the insertion loss requirement of the WiFi device. Furthermore, only one switch is included in the antenna, making the cost of the antenna low. Among them, the insertion loss refers to the insertion loss (insertion loss), also known as the ohmic loss, and the insertion loss of the switch refers to the attenuation of the signal passing through the switch.

Optionally, the first state is an off state, and the second state is an on state.

Optionally, the dipole includes a first radiating arm and a second radiating arm, the second transmission line in the inverted-F structure includes a first feeding part and a second feeding part, and the first transmission line includes a third feeding part and a second feeding part. Four feeders. The second radiating structure is electrically connected to the first radiating structure through the first transmission line, including: one end of the first radiating arm close to the second radiating arm is electrically connected to one end of the third feeding part, and the other end of the third feeding part is connected to the third feeding part through a switch. The first power feeding part is electrically connected; one end of the second radiating arm close to the first radiating arm is electrically connected to the fourth power feeding part, and the other end of the fourth power feeding part is electrically connected to the second power feeding part.

Optionally, the width of the first power feeding part is larger than the width of the third power feeding part, and the width of the second power feeding part is larger than the width of the fourth power feeding part. The first feeder, the second feeder, the third feeder and the fourth feeder are also referred to as feeders.

Generally, the larger the width of the feeder line, the better the impedance matching of the antenna in the low frequency band, and the smaller the width of the feeder line, the better the impedance matching of the antenna in the high frequency band, and the impedance matching at the antenna port is more sensitive. In the antenna provided by the present application, the antenna port is located on the side of the inverted F structure away from the second radiation structure, the width of the first feeding part is larger than the width of the third feeding part, and the width of the second feeding part is larger than that of the fourth feeding part. Therefore, the width of the feeder close to the antenna port in the antenna is greater than the width of the feeder far away from the antenna port, so that the impedance matching at the antenna port of the antenna can be better realized, and the antenna satisfies the impedance matching of the high frequency band and the Impedance matching in the low frequency band, the antenna can meet impedance matching in a wide frequency band.

Optionally, the antenna further includes a carrier substrate, on which the first radiating structure and the second radiating structure are respectively printed.

Optionally, the first radiating arm, the third feeding part, the first feeding part and the matching component in the inverted F structure are respectively printed on one surface of the carrier substrate; the second radiating arm, the fourth feeding part and The second power feeding parts are respectively printed on the other board surface of the carrier substrate.

Optionally, the orthographic projection of the first axis of the first feeder in the reference plane, the orthographic projection of the first axis of the second feeder in the reference plane, and the first axis of the third feeder in the reference plane The orthographic projection in the reference plane and the orthographic projection of the first axis of the fourth feeder in the reference plane are collinear. The first axis of any one of the first feeder, the second feeder, the third feeder and the fourth feeder is parallel to the length direction of the feeder, and the reference plane is parallel to the carrier substrate The boards are parallel.

Optionally, the electrically connecting the circuit board to the inverted F structure through the radio frequency signal port includes: electrically connecting the circuit board to the radio frequency signal line through the radio frequency signal port, and the radio frequency signal line is electrically connected to the inverted F structure. Among them, the radio frequency signal line includes the positive pole line of the radio frequency signal and the negative pole line of the radio frequency signal (also known as the radio frequency signal ground line), the radio frequency signal port includes the positive pole and the negative pole, and the circuit board is electrically connected with the positive pole of the radio frequency signal port through the positive pole of the radio frequency signal port. The signal positive line is electrically connected to the first power feeder in the inverted F structure, the circuit board is electrically connected to the radio frequency signal negative line through the negative pole of the radio frequency signal port, and the radio frequency signal negative line is electrically connected to the second power feeder in the inverted F structure .

Optionally, the first plane and the second plane are two different planes, and the first plane and the second plane may intersect. For example,

The first plane is a horizontal plane, and the second plane is a vertical plane; or, the first plane is a vertical plane, and the second plane is a horizontal plane.

In the technical solution provided by the present application, the first plane is a horizontal plane, and the second plane is a vertical plane; or, the first plane is a vertical plane, and the second plane is a horizontal plane. Therefore, the antenna can radiate electromagnetic waves in the horizontal plane, and can also radiate electromagnetic waves in the vertical plane. The beam that the antenna radiates electromagnetic waves on the horizontal plane is a horizontal beam, and the beam that the antenna radiates electromagnetic waves on a vertical plane is a vertical beam, so the antenna provided by this application can realize the reconstruction of the horizontal beam and the vertical beam.

In a second aspect, a communication device is provided, and the communication device includes the antenna provided by any design in the first aspect.

For the technical effects brought about by the second aspect, reference may be made to the technical effects brought about by the first aspect, which will not be repeated here.

The beneficial effects brought by the technical solution provided by the application are:

The antenna and communication device provided by the present application, because the antenna can radiate electromagnetic waves on the first plane, and can also radiate electromagnetic waves on the second plane, so the beam of the electromagnetic wave radiated by the antenna can realize beam reconstruction, so that it can be based on the home environment, STA The beam coverage of the antenna can be adjusted according to the position of the antenna, and the antenna can be applied to a communication scene in a house with a multi-storey structure. The antenna has high radiation efficiency while realizing beam reconfiguration. The antenna provided in this application can be used for beam coverage requirements of different communication scenarios, and has stronger adaptability to development requirements.

Description of drawings

FIG. 1 is a schematic structural diagram of a smart antenna provided by the related art;

FIG. 2 is a three-dimensional structural diagram of an antenna provided in an embodiment of the present application;

Fig. 3 is a front view of the antenna shown in Fig. 2 provided by an embodiment of the present application;

Fig. 4 is a rear view of the antenna shown in Fig. 2 provided by an embodiment of the present application;

Fig. 5 is a cross-sectional view of the antenna shown in Fig. 2 provided by an embodiment of the present application;

Fig. 6 is a size marking diagram of the antenna shown in Fig. 2 provided by the embodiment of the present application;

Fig. 7 is a front view of an antenna provided by an embodiment of the present application;

Fig. 8 is a front view of another antenna provided by the embodiment of the present application;

FIG. 9 is a schematic diagram of the distribution of current in the antenna when the switch is in the first state provided by the embodiment of the present application;

FIG. 10 is a schematic diagram of the distribution of current in the antenna when the switch is in the second state provided by the embodiment of the present application;

Fig. 11 is a three-dimensional structure diagram of another antenna provided by the embodiment of the present application;

FIG. 12 is an equivalent circuit diagram of the antenna shown in FIG. 11 provided by an embodiment of the present application;

FIG. 13 is a schematic diagram of an S11 curve of the antenna shown in FIG. 11 provided in an embodiment of the present application;

FIG. 14 is a schematic diagram of a Smith chart of the antenna shown in FIG. 11 provided by an embodiment of the present application;

Fig. 15 is an equivalent circuit diagram of the antenna shown in Fig. 2 provided by an embodiment of the present application;

FIG. 16 is a schematic diagram of an S11 curve of the antenna shown in FIG. 2 provided by an embodiment of the present application;

Fig. 17 is a schematic diagram of a Smith chart of the antenna shown in Fig. 2 provided by an embodiment of the present application;

Fig. 18 is a schematic diagram of an S11 curve of an antenna provided in an embodiment of the present application when the antenna is in the first radiation mode;

Fig. 19 is a schematic diagram of an S11 curve of an antenna provided in an embodiment of the present application when the antenna is in the second radiation mode;

Fig. 20 is a comparison diagram of a three-dimensional beam of electromagnetic waves radiated by an antenna in the first radiation mode and a three-dimensional beam of electromagnetic waves radiated by the antenna in the second radiation mode provided by an embodiment of the present application;

Fig. 21 is a comparison diagram of a two-dimensional beam of electromagnetic waves radiated by an antenna in the first radiation mode and a two-dimensional beam of electromagnetic waves radiated by the antenna in the second radiation mode provided by an embodiment of the present application;

Fig. 22 is a comparison diagram of the three-dimensional beam of electromagnetic waves radiated by another antenna in the first radiation mode and the three-dimensional beam of electromagnetic waves radiated by the antenna in the second radiation mode provided by the embodiment of the present application;

Fig. 23 is a comparison diagram of a two-dimensional beam of electromagnetic waves radiated by another antenna in the first radiation mode and a two-dimensional beam of electromagnetic waves radiated by the antenna in the second radiation mode provided by an embodiment of the present application;

Fig. 24 is a comparison diagram between the radiation efficiency of the antenna shown in Fig. 2 and the radiation efficiency of a conventional dipole antenna provided by the embodiment of the present application;

Fig. 25 is a comparison diagram of a three-dimensional beam of electromagnetic waves radiated by the antenna shown in Fig. 2 and a three-dimensional beam of electromagnetic waves radiated by a conventional dipole antenna provided by an embodiment of the present application;

FIG. 26 is a comparison diagram of a two-dimensional beam of electromagnetic waves radiated by the antenna shown in FIG. 2 and a two-dimensional beam of electromagnetic waves radiated by a conventional dipole antenna provided by an embodiment of the present application.

Detailed ways

The embodiments of the present application will be further described in detail below in conjunction with the accompanying drawings.

With the development of communication technology, various communication devices have appeared, such as wireless routers, ONTs, base stations, terminal equipment, etc. The communication device includes an antenna, and the antenna can radiate electromagnetic waves to realize the communication function of the communication device. Wherein, the antenna in the communication device may be an antenna in various forms such as a smart antenna, a printed antenna (also called a printed antenna), and the like.

By way of example, FIG. 1 is a schematic structural diagram of a smart antenna 01 provided in the related art. As shown in FIG. 1 , the smart antenna 01 is arranged on a circuit board A. As shown in FIG. The smart antenna 01 includes a radiation structure 011 , a PIN diode 012 and a matching bridge 013 . The PIN diode 012 is disposed on the radiation structure 011 , and the matching bridge 013 is disposed between the feed point P1 of the radiation structure 011 and the ground point P2 of the radiation structure 011 . The feed point P1 is electrically connected to a radio frequency signal source (not shown in FIG. 1 ) on the circuit board A through the radio frequency signal line A1 , and the ground point P2 is electrically connected to the ground line A2 on the circuit board A.

The radio frequency signal source is used to feed power to the radiation structure 011 through the radio frequency signal line A1, so as to excite the radiation structure 011 to radiate electromagnetic waves. The PIN diode 012 is used to control the smart antenna 01 to switch between the LOOP (loop) radiation mode and the inverted-F antenna (inverted-f antenna, IFA) radiation mode. When the PIN diode 012 is in the conduction state, the smart antenna 01 is in the LOOP radiation mode. When the PIN diode 012 is in the disconnected state, the smart antenna 01 is in the IFA radiation mode. The matching bridge 013 is used to adjust the impedance of the smart antenna 01 to make the impedance of the smart antenna 01 match.

The smart antenna 01 shown in FIG. 1 has high radiation efficiency in different frequency bands. For example, in the global system for mobile communications (GSM) frequency band, the radiation efficiency of the smart antenna 01 is higher than 64.7%. In the global positioning system (global positioning system, GPS) frequency band, data communications system (data communications system, DCS) frequency band, personal communications system (personal communications system, PCS) frequency band and universal mobile telecommunications system (universal mobile telecommunications system, UMTS) frequency band , the radiation efficiency of smart antenna 01 is higher than 47.4%. In the wireless local area network (wirele local area network, WLAN) frequency band, the radiation efficiency of the smart antenna 01 is higher than 62.8%. In view of this, in different frequency bands, the smart antenna 01 can be controlled to be in a radiation mode with higher radiation efficiency (LOOP radiation mode or IFA radiation mode). For example, in a certain frequency band, the radiation efficiency of the smart antenna 01 in the LOOP radiation mode is higher than that of other If the radiation efficiency is in the IFA radiation mode, control the smart antenna 01 to be in the LOOP radiation mode in this frequency band. Thus, the smart antenna 01 can realize frequency band reconfiguration and radiation efficiency reconfiguration.

However, both the LOOP radiation mode and the IFA radiation mode are horizontal radiation modes, and the beams of electromagnetic waves radiated by the smart antenna 01 in these two radiation modes have a high correlation, so that the smart antenna 01 cannot be used for beam reconstruction.

In addition, it can be seen from FIG. 1 that the structure of the smart antenna 01 is a three-dimensional structure, so the installation space of the smart antenna 01 is large. Also, the cost of smart antennas is usually high.

Compared with smart antennas, board-printed antennas have the advantages of low cost, short feeder, simple manufacturing process, and high radiation efficiency, and are widely used in various communication devices. However, current board-printed antennas are usually only able to radiate electromagnetic waves in one plane (for example, the beams of electromagnetic waves radiated by current board-printed antennas are horizontal omnidirectional beams or vertically directional beams), and the electromagnetic waves radiated by this board-printed antenna cannot achieve beam repositioning. structure, its beam coverage cannot be adjusted according to the home environment and the location of the STA, which makes it difficult for the printed board antenna to be suitable for communication scenarios in houses with multi-storey structures such as villas. Alternatively, although some board-printed antennas can realize beam reconfiguration at present, the radiation efficiency of these board-printed antennas is low and the cost is relatively high.

In view of the above problems existing in current antennas, an embodiment of the present application provides an antenna. The antenna includes a first radiating structure, a second radiating structure and a switch. The first radiating structure includes an inverted-F structure and a circuit board, and the circuit board is electrically connected to the inverted-F structure through a radio frequency signal port. The second radiating structure includes a dipole. The second radiating structure is electrically connected to the first radiating structure through the first transmission line. The switches are respectively electrically connected to the first transmission line and the first radiation structure. When the switch is in the first state, the inverted-F structure is used to excite the circuit board to radiate electromagnetic waves on the first plane through the radio frequency signal transmitted to the inverted-F structure. When the switch is in the second state, the first transmission line is used to transmit the radio frequency signal in the inverted F structure to the second radiation structure, and the dipole is excited to radiate electromagnetic waves on the second plane. Since the antenna can radiate electromagnetic waves on the first plane, and can also radiate electromagnetic waves on the second plane, the beam of the electromagnetic wave radiated by the antenna can realize beam reconstruction, thus, the beam coverage of the antenna can be adjusted according to the home environment, STA Position adjustment, etc., the antenna can be applied to communication scenarios in multi-storey houses such as villas. The antenna provided in the embodiment of the present application may be a plate-printed antenna, which has the advantages of low cost, short feeder, simple manufacturing process, and high radiation efficiency. The antenna has high radiation efficiency while realizing beam reconfiguration.

The antenna provided in the embodiment of the present application will be introduced below with reference to the accompanying drawings. To simplify the description, the beam of electromagnetic waves radiated by the antenna is referred to as the beam radiated by the antenna hereinafter. That is, in the following description, the beam radiated by the antenna has the same meaning as the beam of electromagnetic waves radiated by the antenna.

By way of example, FIG. 2 is a three-dimensional structure diagram of an antenna 02 provided by an embodiment of the present application, FIG. 3 is a front view of the antenna 02 shown in FIG. 2 , and FIG. 4 is a rear view of the antenna 02 shown in FIG. 2 , and FIG. 5 is a cross-sectional view of the antenna 02 shown in FIG. 2 (for example, FIG. 5 is a cross-sectional view of a portion a-a in FIG. 3 ). As shown in FIGS. 2 to 5 , the antenna 02 includes a first radiating structure 1 , a second radiating structure 2 and a switch 3 . The first radiating structure 1 includes an inverted-F structure 11 and a circuit board 12. The circuit board 12 is electrically connected to the inverted-F structure 11 through a radio frequency signal port (not shown in FIGS. 2 to 5). The second radiating structure 2 includes a dipole 21 , and the second radiating structure 2 is electrically connected to the first radiating structure 1 through the first transmission line 4 . The switch 3 is electrically connected to the first transmission line 4 and the first radiation structure 1 respectively.

Wherein, when the switch 3 is in the first state, the inverted-F structure 11 is used to excite the circuit board 12 to radiate electromagnetic waves on the first plane through the radio frequency signal transmitted to the inverted-F structure 11 . When the switch 3 is in the first state, the inverted-F structure 11 and the circuit board 12 together form an inverted-F antenna radiation structure, and the inverted-F antenna radiation structure radiates electromagnetic waves on the first plane in the radiation mode of the inverted-F antenna. In an optional embodiment, for example, under the action of the radio frequency signal transmitted to the inverted F structure 11, the inverted F antenna resonance of the required operating frequency band is generated, and the inverted F structure 11 and the circuit board 12 are excited to generate surface currents at the same time. Field forming radiation, ie electromagnetic waves are radiated in the first plane.

Wherein, when the switch 3 is in the second state, the first transmission line 4 is used to transmit the radio frequency signal in the inverted F structure 11 to the second radiation structure 2, and excites the dipole 21 to radiate electromagnetic waves in the second plane. In an optional embodiment, the dipole 21 includes two radiating arms parallel to the length direction, the second plane may be perpendicular to the length direction of the radiating arms of the dipole 21, and the first transmission line 4 reverses the radio frequency in the F structure 11 The signal is transmitted to the dipole 21, and the radio frequency signal in the dipole 21 excites the dipole 21 to radiate electromagnetic waves.

Wherein, the first plane and the second plane are two different planes, and the first plane and the second plane may intersect. For example, the first plane intersects the second plane perpendicularly. In an optional embodiment, the first plane is a horizontal plane, and the second plane is a vertical plane. Alternatively, the first plane is a vertical plane and the second plane is a horizontal plane. A vertical plane refers to a plane perpendicular to a horizontal plane.

Wherein, the electrical connection between the circuit board 12 and the inverted F structure 11 through the radio frequency signal port includes: the circuit board 12 is electrically connected with the radio frequency signal line 6 through the radio frequency signal port, and the radio frequency signal line 6 is electrically connected with the inverted F structure 11 . The radio frequency signal line 6 may be located on the circuit board 12, and the circuit board 12 may also have a radio frequency signal source, and the radio frequency signal port may specifically be a signal port of the radio frequency signal source. The radio frequency signal source can transmit radio frequency signals to the inverted F structure 11 through the radio frequency signal line 6 . Wherein, the radio frequency signal line may include a radio frequency signal positive line and a radio frequency signal negative line, the circuit board 12 is electrically connected to the radio frequency signal positive line and the radio frequency signal negative line respectively through the radio frequency signal port, and the radio frequency signal positive line and the radio frequency signal negative line are respectively connected to the inverted The F structure is electrically connected. The radio frequency signal line 6 shown in FIG. 2 and FIG. 3 is a positive radio frequency signal line, and the negative radio frequency signal line is not shown in FIG. 2 and FIG. 3 .

Wherein, the first state may be an off state, and the second state may be an on state. Referring to FIGS. 2 to 5, when the switch 3 is in the first state (that is, the off state), the radio frequency signal in the inverted F structure 11 cannot be transmitted to the second radiating structure 2 (or in other words, cannot be transmitted to the second radiating structure 2). Partial structure), so the radio frequency signal in the inverted F structure 11 excites the circuit board 12 to radiate electromagnetic waves on the first plane. When the switch 3 is in the second state (that is, the conduction state), the radio frequency signal in the inverted F structure 11 is transmitted to the second radiating structure 2 (or to all structures of the second radiating structure 2) through the first transmission line 4, The radio frequency signal transmitted to the second radiating structure 2 excites the dipole 21 to radiate electromagnetic waves in the second plane. In the embodiment of the present application, the first state is the off state, and the second state is the on state as an example. This does not constitute a limitation on the technical solution of the present application. In other embodiments, the first state may be the on state, The second state may be an off state.

According to the above, it can be known that the antenna 02 provided by the embodiment of the present application has two radiation modes, which are respectively the first radiation mode in which the first radiation structure 1 (specifically, the circuit board 12 in the first radiation structure 1) radiates electromagnetic waves on the first plane. mode, and the second radiation mode in which the second radiating structure 2 (specifically, the dipole 21 in the second radiating structure 2 ) radiates electromagnetic waves in the second plane. The switch 3 can control the antenna 02 to be in the first radiation mode or the second radiation mode, thereby controlling the antenna 02 to radiate electromagnetic waves on the first plane or the second plane. Wherein, the first radiation mode may be an inverted F radiation mode, and the second radiation mode may be a dipole radiation mode. The inverted-F radiation mode refers to the radiation mode of the inverted-F antenna, and the first radiation structure 1 of the embodiment of the present application simulates the inverted-F antenna. The dipole radiation pattern refers to the radiation pattern of a dipole antenna.

To sum up, the antenna provided by the embodiment of the present application can control the antenna to switch between the first radiation mode and the second radiation mode through a switch, thereby controlling the antenna to alternately radiate electromagnetic waves in the first plane and the second plane, because The antenna can radiate electromagnetic waves on the first plane, and can also radiate electromagnetic waves on the second plane, so the beam of the electromagnetic wave radiated by the antenna can realize beam reconstruction, so that the beam coverage of the antenna can be adjusted according to the home environment, the location of the STA, etc. (For example, controlling the antenna to be in the first radiation mode or the second radiation mode according to the home environment, the location of the STA, etc., so as to achieve horizontal beam coverage or vertical beam coverage), the antenna can be applied to communication scenarios in multi-storey houses. The antenna has high radiation efficiency while realizing beam reconfiguration.

As shown in Figures 2 to 5, the inverted F structure 11 includes a second transmission line 111 and two matching components 112, the two matching components 112 are arranged on both sides of the second transmission line 111, and the two matching components 112 are connected to the second transmission line 111 respectively. The two transmission lines 111 are electrically connected. Wherein, the electrical connection of the circuit board 12 with the inverted F structure 11 through the radio frequency signal port includes: the circuit board 12 is electrically connected with the second transmission line 111 through the radio frequency signal port. The embodiment of the present application is illustrated by taking the inverted F structure 11 including two matching components 112 as an example, which does not constitute a limitation to the technical solution of the present application. In other embodiments, the number of matching components 112 in the inverted F structure may be greater than two , which is not limited in this embodiment of the present application.

As shown in FIGS. 2 to 5 , the second transmission line 111 includes a first feeder 1111 and a second feeder 1112 , and the first feeder 1111 and the second feeder 1112 are located in two parallel planes. For example, the antenna 02 further includes a carrier substrate 5, the carrier substrate 5 has two parallel board surfaces, and the first feeding part 1111 and the second feeding part 1112 are located in two parallel planes including: the first feeding part 1111 is set On one board surface (for example, the first board surface) of the carrier substrate 5 , the second power feeding part 1112 is disposed on the other board surface (for example, the second board surface) of the carrier substrate 5 .

Wherein, the two matching components 112 disposed on both sides of the second transmission line 111 include: the two matching components 112 disposed on both sides of the first power feeding part 1111 . The two matching components 112 and the first power feeding part 1111 may be located in the same plane. For example, the two matching components 112 and the first power feeding portion 1111 are both disposed on the first board surface of the carrier substrate 5 .

Wherein, the electrical connection of the circuit board 12 with the second transmission line 111 through the radio frequency signal port includes: the circuit board 12 is electrically connected with the radio frequency signal line through the radio frequency signal port, and the radio frequency signal line is respectively connected with the first power feeding part 1111 and the second power feeding part 1112 electrical connection. For example, the radio frequency signal port can include a positive pole and a negative pole, the radio frequency signal line can include a radio frequency signal positive pole line and a radio frequency signal negative pole line, the first feeder 1111 can be a positive pole feeder, and the second power feeder 1112 can be a negative pole feeder The circuit board 12 is electrically connected to the radio frequency signal line through the radio frequency signal port, including: the circuit board 12 is electrically connected to the radio frequency signal positive line through the positive pole of the radio frequency signal port, and the circuit board 12 is electrically connected to the radio frequency signal negative line through the negative pole of the radio frequency signal port The radio frequency signal line is electrically connected to the first power feeding part 1111 and the second power feeding part 1112 respectively, including: the radio frequency signal positive line is electrically connected to the first power feeding part 1111, and the radio frequency signal negative line is electrically connected to the second power feeding part 1112 . The radio frequency signal line 6 shown in FIG. 2 and FIG. 3 may be a positive radio frequency signal line, and the negative radio frequency signal line is not shown in FIG. 2 and FIG. 3 .

As shown in FIGS. 2 to 5 , each of the two matching components 112 includes a first matching stub 1121 and a second matching stub 1122 . In each matching component 112 , one end of the first matching branch 1121 is electrically connected to the middle of the second matching branch 1122 , and the other end of the first matching branch 1121 is grounded. For example, there is a ground wire on the circuit board 12 (not shown in FIGS. One end is grounded through the ground wire on the circuit board 12 . Wherein, the length range of the first matching stub 1121 is (0, λ/4), and λ is the working wavelength of the electromagnetic wave radiated by the antenna 02 . The two matching components 112 are respectively electrically connected to the second transmission line 111 including: for each matching component 112 in the two matching components 112, one end of the second matching branch 1122 of the matching component 112 is connected to the first power feeding part 1111 electrical connection.

In the embodiment of the present application, the two matching components 112 are roughly symmetrical with respect to the first power feeding part 1111 . Optionally, the difference in distance between the first matching stub 1121 of the two matching components 112 and the first power feeding part 1111 is smaller than the first difference threshold, and the length of the second matching stub 1122 of the two matching components 112 is The difference is less than the second difference threshold, and the projected length of the distance between the second matching branch 1122 of the two matching components 112 and the connection position of the first power feeding part 1111 in the first direction in the first direction is less than the first distance threshold, The first direction is parallel to the length direction of the first transmission line 4 . As an example, FIG. 6 is a size identification diagram of an antenna 02 provided in the embodiment of the present application. As shown in FIG. The distances are s1 and s2 respectively, the lengths of the two second matching branches 1122 of the two matching parts 112 are respectively s3 and s4, and the connection position between the two second matching branches 1122 and the first power feeding part 1111 The distance between s1 and s2 is less than the first difference threshold, the difference between s3 and s4 is less than the second difference threshold, and the projected length of the distance s5 in the first direction h is less than the first distance threshold. In this embodiment of the application, as shown in FIG. 6 , the distance between any matching branch 1121 and the first power feeding part 1111 refers to: the side of the matching branch 1121 close to the first power feeding part 1111 and the The distance between the sides of the first power feeding part 1111 that is close to the matching stub 1121 . In other embodiments, the distance between any matching branch 1121 and the first feeding part 1111 may also be: the distance between the axis of the matching branch 1121 and the axis of the first feeding part 1111, or the The distance between the side of the matching stub 1121 close to the first power feeding part 1111 and the axis of the first power feeding part 1111 , or other similar definitions, is not limited in this embodiment of the present application. Wherein, the first difference threshold, the second difference threshold and the first distance threshold can all be set according to actual conditions, for example, the first difference threshold, the second difference threshold and the first distance threshold are all 0.

As shown in FIGS. 2 to 5 , the first transmission line 4 includes a third feeder 41 and a fourth feeder 42 , and the third feeder 41 and the fourth feeder 42 are located in two parallel planes. For example, the third power feeding part 41 is located in the same plane as the first power feeding part 1111 , and the fourth power feeding part 42 is located in the same plane as the second power feeding part 1112 . In an optional embodiment, the third power feeding part 41 and the first power feeding part 1111 are arranged on a board surface (for example, the first board surface) of the carrier substrate 5, and the fourth power feeding part 42 and the second power feeding part 1112 is disposed on the other board surface (for example, the second board surface) of the carrier substrate 5 .

Wherein, the switch 3 being electrically connected to the first transmission line 4 and the first radiation structure 1 respectively includes: the switch 3 being electrically connected to the third feeding part 41 and the inverted-F structure 11 respectively. Optionally, there is a gap between the third power feeding part 41 and the inverted-F structure 11, and the switch 3 is connected across the gap, so that the switch 3 is electrically connected to the third power feeding part 41 and the inverted-F structure 11 respectively. Optionally, the inverted-F structure 11 includes a first power feeding part 1111, and having a gap between the third power feeding part 41 and the inverted-F structure 11 includes: having a gap between the third power feeding part 41 and the first power feeding part 1111 . The switch 3 may be connected across the gap between the third power feeding part 41 and the first power feeding part 1111 . Wherein, the width of the gap can be determined according to the packaging requirements of the switch 3 . For example, the switch 3 is a PIN diode, and the width of the gap is 0.5mm˜1.0mm. In an optional embodiment, the width of the gap may be 1.0mm.

As shown in FIGS. 2 to 5 , the dipole 21 includes a first radiating arm 211 and a second radiating arm 212 , and the second transmission line 111 in the inverted-F structure 11 includes a first feeding part 1111 and a second feeding part 1112 , the first transmission line 4 includes a third feeder 41 and a fourth feeder 42 . The second radiating structure 2 is electrically connected to the first radiating structure 1 through the first transmission line 4, including: one end of the first radiating arm 211 close to the second radiating arm 212 is electrically connected to one end of the third feeding part 41, and the third feeding part The other end of 41 is electrically connected to the first power feeding part 1111 through the switch 3, one end of the second radiating arm 212 close to the first radiating arm 211 is electrically connected to the fourth power feeding part 42, and the other end of the fourth power feeding part 42 is connected to the The second power feeding part 1112 is electrically connected.

In the embodiment of the present application, the width of the first power feeding portion 1111 is greater than that of the third power feeding portion 41 , and the width of the second power feeding portion 1112 is greater than that of the fourth power feeding portion 42 . Optionally, the width of the first power feeding part 1111 is equal to the width of the second power feeding part 1112 , and the width of the third power feeding part 41 is equal to the width of the fourth power feeding part 42 . Wherein, the width of any one of the first feeder 1111, the second feeder 1112, the third feeder 41, and the fourth feeder 42 refers to the width of the feeder in the second direction. , the second direction is perpendicular to the first direction h (as shown in FIG. 5 ), and the second direction is parallel to the surface of the carrier substrate 5 . In some embodiments, the first feeder 1111 , the second feeder 1112 , the third feeder 41 and the fourth feeder 42 are also referred to as feeders. Generally, the larger the width of the feed line, the better the impedance matching of the antenna in the low frequency band, the smaller the width of the feed line, the better the impedance matching of the antenna in the high frequency band, and the impedance matching at the antenna port (also known as the feed point) is more sensitive . In the antenna 02 provided in the embodiment of the present application, the antenna port is located on the side of the inverted F structure 11 away from the second radiation structure 2, the width of the first feeding part 1111 is larger than the width of the third feeding part 41, and the second feeding part 1111 The width of the part 1112 is greater than the width of the fourth feeding part 42, so the width of the feeder close to the antenna port in the antenna 02 is greater than the width of the feeder far away from the antenna port, so that the antenna 02 can better achieve impedance matching at the antenna port , and the antenna 02 satisfies the impedance matching of the high frequency band and the impedance matching of the low frequency band, and the antenna 02 can satisfy the impedance matching in a wide frequency band.

In the embodiment of the present application, the antenna 02 may be a plate-printed antenna, and the first radiating structure 1 and the second radiating structure 2 are printed on the carrier substrate 5 respectively. For example, the first radiating arm 211, the third feeding part 41, the first feeding part 1111 and the matching component 112 are respectively printed on a board surface (such as the first board surface) of the carrier substrate 5, and the second radiating arm 212, The fourth power feeding part 42 and the second power feeding part 1112 are respectively printed on the other board surface (for example, the second board surface) of the carrier substrate 5 . The orthographic projection of the first axis of the first feeding part 1111 in the reference plane, the orthographic projection of the first axis of the second feeding part 1112 in the reference plane, the first axis of the third feeding part 41 in the reference plane The orthographic projection in the plane and the orthographic projection of the first axis of the fourth feeder 42 in the reference plane are collinear, the first feeder 1111, the second feeder 1112, the third feeder 41 and the fourth The first axis of any one of the feeders 42 is parallel to the length direction of the feeder (for example, the first direction h shown in FIG. 6 ), and the reference plane is parallel to the surface of the carrier substrate 5 .

Optionally, the number of switches 3 is one. Since there is insertion loss when the switch is in the on state, the insertion loss easily affects the radiation efficiency of the antenna, and this effect is particularly obvious in the fifth generation mobile communication technology (5G) frequency band. Moreover, if the insertion loss in the antenna is large, it is easy to cause the antenna to fail to meet the insertion loss requirement of the WiFi device. The antenna 02 provided by the embodiment of the present application only includes one switch 3, and the number of switches in the antenna 02 is small, so the insertion loss in the antenna 02 is small, and the insertion loss has little influence on the radiation efficiency of the antenna 02, which is helpful To ensure the radiation efficiency of the antenna 02. Moreover, since the antenna 02 only includes one switch 3, the antenna 02 can meet the insertion loss requirement of the WiFi device. In addition, only one switch 3 is included in the antenna 02, so that the cost of the antenna 02 is low. Wherein, insertion loss refers to insertion loss, and insertion loss of a switch refers to attenuation of a signal passing through the switch.

In an optional embodiment, a bias circuit may be used to supply power to the switch 3 so that the switch 3 can work. Wherein, the bias circuit has two ports, one of which is electrically connected to the anode of the switch 3 , and the other is grounded. The bias circuit may include two low-current inductors and a current-limiting resistor, and the two low-current inductors and the one current-limiting resistor are connected in series in sequence. The inductance of the two low-current inductors can range from 5.1nH to 5.6nH (nanohenry), and the conduction current of the switch 3 can range from 5mA to 10mA (milliampere). For example, the inductances of the two low-current inductors are both 5.1nH, the resistance of the current-limiting resistor is 80ohm (ohm), the conduction voltage of the switch 3 is 0.86V (volt), and the maximum current is 10mA.

Wherein, the switch 3 may be a PIN diode. The PIN diode is a microwave switch, and the resistance of the PIN diode is determined by the DC bias voltage. When the DC bias voltage of the PIN diode is a forward bias voltage, the resistance value of the PIN diode is minimum, the PIN diode is close to a short circuit, and the PIN diode is turned on. When the DC bias voltage of the PIN diode is a reverse bias voltage, the resistance of the PIN diode is the largest, the PIN diode is close to an open circuit, and the PIN diode is disconnected. The PIN diode realizes the conversion of the controlled microwave signal channel by utilizing its impedance characteristics of being approximately on or off under DC forward and reverse bias voltages. The PIN diode does not produce a nonlinear rectification effect on the microwave signal. The embodiment of the present application uses the PIN diode as the switch 3 in the antenna 02 to control the switching of the radiation mode of the antenna 02, which can avoid the microwave signal (such as a radio frequency signal) passing through the switch 3. ), so as to avoid the influence on the radiation efficiency of antenna 02. In this embodiment of the present application, the switch 3 is a PIN diode as an example for illustration. In other embodiments, the switch 3 may also be other devices that can be used to turn on or off the signal, which is not limited in this embodiment of the present application.

In the embodiment of the present application, the circuit board 12 can be a rectangular board, the inverted F structure 11, the second radiation structure 2 and the first transmission line 4 are located on the same side of the circuit board 12, and the second radiation structure 2 is located on the inverted F structure 11 On the side away from the circuit board 12 , the first transmission line 4 is located between the second radiating structure 2 and the inverted-F structure 11 . As shown in FIG. 7 , the inverted-F structure 11 , the second radiating structure 2 and the first transmission line 4 are all located on the side where the top edge of the circuit board 12 is located. Alternatively, the inverted F structure 11 , the second radiating structure 2 and the first transmission line 4 are all located on the side where the side of the circuit board 12 is located. For example, as shown in FIG. 8 , the inverted-F structure 11 , the second radiating structure 2 and the first transmission line 4 are all located on the left side of the circuit board 12 . The inverted F structure 11 , the second radiation structure 2 and the first transmission line 4 may also be located on the right side of the circuit board 12 , which is not limited in this embodiment of the present application. Wherein, the top side of the circuit board 12 refers to the side of the circuit board 12 away from the placement surface when the circuit board 12 is placed in the forward direction. The side of the circuit board 12 refers to the side of the circuit board 12 intersecting with the placement surface when the circuit board 12 is placed in the forward direction. The forward placement of the circuit board 12 is, for example, the forward placement of the communication device including the circuit board 12 . The communication device may include a base, through which the communication device is placed forwardly, for example, the communication device is placed on a placement surface.

In the embodiment of the present application, the circuit board 12 may be a printed circuit board (printed circuit board, PCB), and the circuit board 12 includes a carrier substrate and a circuit on the carrier substrate. The carrier substrate of the circuit board 12 and the carrier substrate 5 of the antenna 02 may be the same substrate. Optionally, the carrier substrate 5 is a double-sided copper-clad plate, as shown in Figure 7 and Figure 8, the carrier substrate 5 includes a copper-clad area Q1 and a clearance area Q2, the clearance area Q2 can surround the copper-clad area Q1, and the circuit board The circuit of 12 may be located in the copper clad area Q1, and the inverted F structure 11 of the antenna 02, the second radiation structure 2 and the first transmission line 4 are all located in the clearance area Q2. The circuit board 12 may include a portion of the carrier substrate 5 corresponding to the copper clad area Q1 and a copper layer located in the copper clad area Q1 . As shown in Figure 7 and Figure 8, the carrier substrate 5 and the circuit board 12 are both rectangular plates, the length of the circuit board 12 (specifically the length of the copper clad area Q1) is L1, and the width of the circuit board 12 (specifically the length of the copper clad area The width of Q1) is L2, the length of the dipole 21 is L3, the distance between the dipole 21 and the circuit board 12 is L4, the length of the first matching stub 1121 is L5, the third feeding part 1111 and the The length of the overall structure formed by the two second matching branches 1122 connected by the three feeders 1111 is L6, and the width of the third feeder 1111 is L7. In a specific example, L1=200mm, L2=140mm, L3=20mm, L4=12mm, L5=3.4mm, L6=18.8mm, L7=3.7mm.

As mentioned before, the first state is the off state and the second state is the on state. Please refer to FIG. 9 and FIG. 10. FIG. 9 is a schematic diagram of the current distribution in the antenna 02 when the switch 3 is in the first state provided by the embodiment of the present application. FIG. Schematic diagram of current distribution in antenna 02 in two states. The arrows in FIG. 9 and FIG. 10 indicate the direction of current transmission, and the density of the arrows indicates the intensity of the current. Referring to FIG. 9 in conjunction with FIGS. 2 to 5 , when the switch 3 is in the first state (that is, the off state), the radio frequency signal (that is, the radio frequency current) in the inverted F structure 11 cannot be transmitted to the first A radiating arm 211, so the current in the first radiating arm 211 (this current is an induced current) is very weak, the dipole radiation mode of the antenna 02 is not excited, and the radio frequency signal in the inverted F structure 11 excites the circuit board 12 A plane radiates electromagnetic waves, the current in the inverted F structure 11 and the circuit board 12 (this current is radio frequency current) is strong, and the antenna 02 is in the inverted F radiation mode. It should be noted that when the switch 3 is in the off state, since the second radiating arm 212 is electrically connected to the inverted-F structure 11 through the fourth feeding part 42, the radio frequency signal in the inverted-F structure 11 can pass through the fourth feeding part 42 transmitted to the second radiating arm 212, so the current in the second radiating arm 212 (this current is a radio frequency current) is relatively strong, and in the inverted F structure 11, the second feeding part 1112, the fourth feeding part 42 and the second Under the action of the radiating arm 212 , there is a weak induced current in the first radiating arm 211 , but because the induced current in the first radiating arm 211 is very weak, the dipole radiation mode of the antenna 02 is not excited. Referring to FIG. 10 in conjunction with FIGS. 2 to 5 , when the switch 3 is in the on state, the radio frequency signal (that is, the radio frequency current) in the inverted F structure 11 is transmitted to the first radiating arm 211 through the third feeding part 41, and the inverted F The radio frequency signal (that is, the radio frequency current) in the structure 11 is transmitted to the second radiating arm 212 through the fourth feeding part 42, the first radiating arm 211 and the second radiating arm 212 have the same direction and equal amplitude radio frequency current, the first radiating The radio frequency current in the arm 211 and the second radiating arm 212 is strong, the dipole radiation mode of the antenna 02 is excited, the dipole 21 radiates electromagnetic waves in the second plane, and the antenna 02 is in the dipole radiation mode.

In the embodiment of the present application, for the antenna 02 (such as the antenna 02 shown in FIG. is the horizontal plane, and the second plane is the vertical plane. For the antenna 02 (such as the antenna 02 shown in FIG. 8 ) where the inverted F structure 11, the second radiating structure 2, and the first transmission line 4 are all located at the side of the circuit board 12, the first plane is a vertical plane, and the second plane for the horizontal plane. The beam radiated by the antenna on the horizontal plane is the horizontal beam, and the beam radiated by the antenna on the vertical plane is the vertical beam. In the first radiation mode (ie, the inverted F radiation mode), the working frequency band of the antenna 02 may be 5.0 GHz˜6.6 GHz (gigahertz). In the second radiation mode (ie, the dipole radiation mode), the working frequency band of the antenna 02 may be 5.0 GHz˜6.1 GHz (gigahertz). Take the first state as an off state and the second state as an on state as an example. For the antenna 02 where the inverted-F structure 11, the second radiating structure 2 and the first transmission line 4 are all located on the side where the top edge of the circuit board 12 is located, the state of the switch 3, the radiation pattern of the antenna 02, the beam radiated by the antenna 02 and the The working frequency band may be shown in Table 1 below. For the antenna 02 with the inverted F structure 11, the second radiating structure 2 and the first transmission line 4 all located on the side of the circuit board 12, the state of the switch 3, the radiation pattern of the antenna 02, the beam radiated by the antenna 02 and the The working frequency band may be shown in Table 2 below. In Table 1 and Table 2 below, "0" indicates that the switch 3 is in an off state, and "1" indicates that the switch 3 is in an on state.

Table 1

switch status	radiation pattern	radiation beam	Working frequency(GHz)
0	First Radiation Mode (Inverted F Radiation Mode)	horizontal beam	5.0～6.6
1	Second Radiation Mode (Dipole Radiation Mode)	vertical beam	5.0～6.1

Table 2

switch status	radiation pattern	radiation beam	Working frequency(GHz)
0	First Radiation Mode (Inverted F Radiation Mode)	vertical beam	5.0～6.6
1	Second Radiation Mode (Dipole Radiation Mode)	horizontal beam	5.0～6.1

In the embodiment of the present application, the matching component 112 can not only be used to construct the inverted F structure 11, but also can be used to adjust the impedance of the antenna 02, so that whether the antenna 02 is in the first radiation mode (ie, the inverted F radiation mode) or the second radiation mode Mode (ie, dipole radiation mode), in the working frequency band of antenna 02, the return loss (ie, S11) of antenna 02 is smaller than the preset loss. For example, the preset loss is -10dB. Among them, return loss is also called reflection loss, which refers to the reflection loss caused by impedance mismatch. The return loss of the antenna refers to the return loss of the antenna port. The return loss of the antenna can be the ratio of the reflected signal power of the antenna port to the incident signal power, for example, the power of the radio frequency signal reflected from the antenna port and the input signal The ratio of the power of the RF signal at the antenna port. In some embodiments, the antenna port is also referred to as the feeding point of the antenna. The content of adjusting the impedance of the antenna 02 by the matching component 112 will be described below with reference to the accompanying drawings.

Assuming that the antenna 02 does not include the matching component 112, the antenna 02 is simplified as the antenna shown in FIG. 11 (for ease of distinction, the antenna shown in FIG. 11 is marked as the antenna 03). Referring to FIG. 11 , when the switch 3 is in the off state, the feeder 111 (including the third feeder 1111 and the fourth feeder 1112 ), the feeder 42, the second radiating arm 212 and the circuit board 12 constitute a single unit. Pole radiation structure, antenna 03 is in monopole radiation mode. When the switch 3 is in the on state, the dipole 21 radiates electromagnetic waves, and the antenna 03 is in the dipole radiation mode. When the switch 3 is in the off state, the equivalent circuit of the antenna 03 is shown in FIG. 12 . In the equivalent circuit shown in FIG. 12 , the coupling capacitance is the coupling capacitance formed by the third feeder 1111 and the fourth feeder 1112 in the antenna 03 , and the load impedance refers to the load impedance of air. It should be noted that the antenna is a single-port device, one end of the antenna (i.e., the antenna port) is connected to the radio frequency signal source, and the other ends (such as the end of the first radiating arm 211 away from the second radiating arm 212, and the end of the second radiating arm 212 away from the One end of the first radiation arm 211) and the antenna port are open, and the load impedance refers to the load impedance of the air between the antenna port and the rest of the antenna. Figure 13 is a schematic diagram of the S11 curve of the antenna 03 shown in Figure 11 when the switch 3 of the antenna 03 is in the off state. The wave loss is much greater than -10dB, so the impedance of antenna 03 is severely mismatched. Fig. 14 is a schematic diagram of the S11 curve of the antenna 03 in the Smith chart when the switch 3 of the antenna 03 shown in Fig. 11 is in an off state, and S11 (50Ohm) represents that the port impedance of the radio frequency signal source feeding the antenna 03 is 50Ohm When the S11 curve of the antenna 03 is measured, the input impedance of the antenna is also about 50Ohm, which can ensure that the return loss of the antenna is less than -10dB. In Figure 14, the frequency corresponding to point A is 4.9886GHz, and the frequency corresponding to point B is 6.0058GHz, and the corresponding frequency from point A to point B in the S11 curve increases in turn. It can be seen from the Smith chart shown in Figure 14 that the S11 curve of antenna 03 (the part of the S11 curve shown in Figure 14 between points A and B) in the 5G working frequency band (5G-6G frequency band) deviates seriously The origin of the Smith chart (that is, the center point of the Smith chart, such as the center point of the largest circle in Figure 14), and the S11 curve of antenna 03 in the 5G working frequency band is located in the left semicircle of the Smith chart. The S11 curve of the low-frequency antenna 03 in the 5G-6G frequency band is located in the lower semicircle of the Smith chart, so the low-frequency antenna 03 in the 5G-6G frequency band is capacitive (the lower half circle of the Smith chart is the capacitive area) . The S11 curve of the high-frequency antenna 03 in the 5G-6G frequency band is located in the upper semicircle of the Smith chart, so the high-frequency antenna 03 in the 5G-6G frequency band is inductive (the upper semicircle of the Smith chart is the perceptual area). In Figure 14, (3.187648, -6.082366) Ohm represents the antenna impedance corresponding to point A (the value of the antenna impedance corresponding to point A is

3.187648 is the value of the real part of the antenna impedance corresponding to point A, indicating that the resistance of the antenna impedance corresponding to point A is 3.187648Ohm, -6.082366 is the value of the imaginary part of the antenna impedance corresponding to point A, indicating that the resistance of the antenna impedance corresponding to point A is The difference between the inductive reactance and the capacitive reactance in the antenna impedance, the difference between the inductive reactance and the capacitive reactance corresponding to point A is -6.082366Ohm, indicating that the capacitive reactance corresponding to point A is greater than the inductive reactance, so the frequency corresponding to point A (49886GHz ) Antenna 03 is capacitive. Similarly, (3.667941, 9.485762) Ohm represents the antenna impedance corresponding to point B (the value of the antenna impedance corresponding to point B is

3.667941 is the value of the real part of the antenna impedance corresponding to point B, indicating that the resistance of the antenna impedance corresponding to point B is 3.667941Ohm, 9.485762 is the value of the imaginary part of the antenna impedance corresponding to point B, indicating the antenna corresponding to point B The difference between the inductive reactance and the capacitive reactance in the impedance, the difference between the inductive reactance and the capacitive reactance corresponding to point B is 9.485762hm, indicating that the inductive reactance corresponding to point B is greater than the capacitive reactance, so the frequency corresponding to point B (6.0058GHz) Antenna 03 is inductive. Since the frequency corresponding to point A to point B in the S11 curve increases sequentially, it can be determined that the antenna 03 is capacitive in the low frequency band of the 5G~6G frequency band, and the antenna 03 is inductive in the high frequency band of the 5G~6G frequency band. . Since the S11 curve of the antenna 03 in the 5G working frequency band is located in the left semicircle of the Smith chart, and the antenna 03 is capacitive in the low frequency band of the 5G~6G frequency band, and the antenna 03 is inductive in the high frequency band of the 5G~6G frequency band , therefore, parallel inductors and parallel capacitors can be constructed in the antenna 03, so that the antenna 03 can satisfy impedance matching when the switch 3 is in the off state.

In the embodiment of the present application, the antenna 02 shown in FIG. 2 is obtained by adding two matching components 112 to the antenna 03 shown in FIG. 10 , and the two matching components 112 construct a parallel inductor and a parallel capacitor. As mentioned above, the two matching components 112 respectively include a first matching stub 1121 and a second matching stub 1122 . In the embodiment of the present application, each first matching stub 1121 is equivalent to a matching inductor, and each second matching stub 1122 and the circuit board 12 are equivalent to a matching capacitor. For the antenna 02 shown in FIG. 2 , the equivalent circuit of the antenna 02 is shown in FIG. 15 when the switch 3 is in the off state. Fig. 16 is a schematic diagram of an S11 curve of the antenna 02 shown in Fig. 2 when the switch 3 of the antenna 02 is in the off state. As shown in Fig. 16, the return loss of the antenna 02 is Both are less than -10dB, so the impedance of the antenna 02 is matched in the 5G working frequency band (for example, the 5G-6G frequency band). FIG. 17 is a schematic diagram of the S11 curve of the antenna 02 in the Smith chart when the switch 3 of the antenna 02 shown in FIG. 2 is in the off state. S11(50Ohm) represents the S11 curve of the antenna 02 measured when the port impedance of the radio frequency signal source feeding the antenna 02 is 50Ohm. In Figure 17, the frequency corresponding to point A is 49886GHz, and the frequency corresponding to point B is 6.0058GHz. Antenna impedance, (32.239287, -3.116502) Ohm represents the antenna impedance corresponding to point B. It can be seen from the Smith chart shown in Figure 17 that the S11 curve of antenna 02 in the 5G working frequency band (the part of the S11 curve shown in Figure 17 between points A and B) is distributed up and down around the origin of the Smith chart , which is due to the effect of the parallel inductance and parallel capacitance constructed by the two matching components 112 on the impedance adjustment of the antenna 02 .

For example, FIG. 18 is a schematic diagram of the S11 curve of the antenna 02 when the antenna 02 is in the first radiation mode (the switch 3 is in the off state). When the antenna 02 is in the first radiation mode, the working frequency band of the antenna 02 may be 5.0GHz˜6.6GHz. As shown in Figure 18, in the frequency band of 4.9416GHz to 6.6261GHz, the return loss of antenna 02 is less than -10dB, so the return loss of antenna 02 is less than - 10dB. FIG. 19 is a schematic diagram of the S11 curve of the antenna 02 when the antenna 02 is in the second radiation mode (the switch 3 is in the on state). When the antenna 02 is in the second radiation mode, the working frequency band of the antenna 02 may be 5.0 GHz˜6.1 GHz. As shown in Figure 19, in the frequency band of 4.9886GHz to 6.0058GHz, the return loss of antenna 02 is basically less than -10dB, so the return loss of antenna 02 in the working frequency band of antenna 02 (5.0GHz to 6.1GHz) is basically Both are less than -10dB. According to Fig. 19, in the working frequency band of antenna 02, there are a small number of frequency points corresponding to return loss (namely S11) greater than -10dB, so the return loss of antenna 02 at these frequency points is greater than -10dB. In practical applications, the working frequency of the antenna 02 can be controlled within the working frequency band of the antenna 02 to avoid these frequency points corresponding to S11 greater than -10dB, so as to ensure that the return loss of the antenna 02 at the working frequency of the antenna 02 is less than -10dB.

As mentioned above, in the antenna 02 provided in the embodiment of the present application, the inverted F structure 11, the second radiation structure 2 and the first transmission line 4 may be located on the side where the top edge of the circuit board 12 is located (for example as shown in FIG. 7 ). Alternatively, the inverted-F structure 11 , the second radiation structure 2 and the first transmission line 4 may be located on the side of the circuit board 12 (such as shown in FIG. 8 ). Depending on the positions of the inverted-F structure 11 , the second radiating structure 2 and the first transmission line 4 relative to the circuit board 12 , beams of electromagnetic waves radiated by the antenna 02 are different. The beam of the electromagnetic wave radiated by the antenna 02 when the inverted F structure 11, the second radiating structure 2 and the first transmission line 4 are located on the side where the top edge of the circuit board 12 is located, and the inverted F structure 11 and the second radiating structure 2 will be described below in conjunction with the accompanying drawings. And the first transmission line 4 can be described as the electromagnetic wave beam radiated by the antenna 02 when the left side of the circuit board 12 is located.

Exemplarily, FIG. 20 is a three-dimensional beam of electromagnetic waves radiated by antenna 02 in the first radiation mode (ie, inverted F radiation mode, switch 3 is in the off state) and antenna 02 in the second radiation mode provided by the embodiment of the present application. (that is, the dipole radiation mode, the switch 3 is in the ON state) the comparison diagram of the three-dimensional beam of the radiated electromagnetic wave (that is, the comparison diagram of the three-dimensional pattern of the beam). Fig. 21 is a comparison diagram of a two-dimensional beam of electromagnetic waves radiated by the antenna 02 in the first radiation mode and a two-dimensional beam of electromagnetic waves radiated by the antenna 02 in the second radiation mode provided by an embodiment of the present application (that is, the beam Comparison diagram of 2D pattern). 20 and 21 correspond to the situation where the inverted F structure 11 , the second radiating structure 2 and the first transmission line 4 are located on the side where the top edge of the circuit board 12 is located. When the inverted F structure 11, the second radiating structure 2 and the first transmission line 4 are located on the side where the top edge of the circuit board 12 is located, the beam radiated by the antenna 02 in the first radiation mode is a horizontal beam, and the antenna 02 radiates in the second radiation mode The beam is a vertical beam. In Fig. 20, beam a1, beam a2 and beam a3 are all beams (horizontal beams) radiated by antenna 02 in the first radiation mode, and beam a4, beam a5 and beam a6 are all beams radiated by antenna 02 in the second radiation mode Beams (vertical beams), beam a1 and beam a4 correspond to 5.1 GHz, beam a2 and beam a5 correspond to 5.5 GHz, beam a3 and beam a6 correspond to 5.8 GHz GHz. In FIG. 21 , each of comparative case a1, comparative case a2, and comparative case a3 is the beam (horizontal beam) radiated by antenna 02 in the first radiation mode and the beam radiated by antenna 02 in the second radiation mode (vertical beam) contrast in the horizontal plane (xoz plane). Each of the comparative case a4, comparative case a5 and comparative case a6 is that the beam (horizontal beam) radiated by the antenna 02 in the first radiation mode and the beam (vertical beam) radiated by the antenna 02 in the second radiation mode are at Contrast in the vertical plane (yoz plane). The corresponding operating frequencies of comparative case a1 and comparative case a4 are both 5.1GHz, the corresponding operating frequencies of comparative case a2 and comparative case a5 are both 5.5GHz, and the corresponding operating frequencies of comparative case a3 and comparative case a6 are both 5.8GHz . The beams in FIG. 20 are three-dimensional beams, and the beams in FIG. 21 are two-dimensional beams. Each two-dimensional beam in FIG. 21 is a corresponding three-dimensional beam in FIG. 20 in a corresponding plane. For example, the horizontal beam shown by the black solid line in the comparative case a1 in Fig. 21 is the beam in the horizontal plane (xoz plane) of the beam a1 in Fig. 20, and the vertical beam shown by the black dotted line in the comparative case a1 in Fig. 21 is the beam in the horizontal plane (xoz plane) of beam a4 in FIG. 20 . For another example, the horizontal beam shown by the black solid line in the comparative case a4 of Figure 21 is the beam of the beam a1 in Figure 20 in the vertical plane (yoz plane), and the black dotted line in the comparative case a4 of Figure 21 shows The vertical beam is the beam a4 in FIG. 20 in the vertical plane (yoz plane). Wherein, the working frequency point corresponding to any comparison situation refers to the working frequency point corresponding to the beam in the comparison situation. The working frequency point corresponding to any beam refers to the working frequency point of the antenna, and the beam is the beam radiated by the antenna working at the working frequency point. For example, beam a1 is a horizontal beam radiated by antenna 02 working at 5.1 GHz. It can be seen from Fig. 20 and Fig. 21 that the gain of the horizontal beam (the beam radiated by the antenna 02 in the first radiation mode) is quite different from the gain of the vertical beam (the beam radiated by the antenna 02 in the second radiation mode), The difference between the characteristics of the horizontal beam and the characteristics of the vertical beam is more obvious. It can be seen from Fig. 21 that in the horizontal plane (xoz plane), the gain of the horizontal beam and the gain of the vertical beam trade off each other, and the gain of the vertical beam is smaller when the gain of the horizontal beam is larger (for example, in the case The gain (3.162dB) corresponding to point C in the direction of -90 degrees is larger than the gain (-1.707dB) corresponding to point A), so the horizontal beam and the vertical beam present complementary characteristics. The leftward gain of the horizontal beam in the horizontal plane (the direction from the origin to -90 degrees in each direction diagram of the horizontal plane in Figure 21 is the leftward direction, and the origin of the direction diagram is the center of the circle) is 4.3 higher than the leftward gain of the vertical beam dB～9.0dB(4.3dB≈3.925dB-(-0.3503)dB=4.2753dB, 3.925 is the gain of point C in the comparative case a3 of Figure 21, and -0.3503 is the gain of point A in the comparative case a3 of Figure 21 ; 9.0dB≈3.162dB-(-5.826)dB=8.988dB, 3.162 is the gain of point C in the comparative case a1 of Figure 21, and -5.826 is the gain of point A in the comparative case a1 of Figure 21), in the horizontal plane The front-to-back gain of the inner vertical beam (the direction from the origin to 0 degrees is the forward direction, and the direction from the origin to 180 degrees is the backward direction in the various direction diagrams of the horizontal plane in Figure 21) is higher than that of the horizontal beam . The gain of the vertical beam is higher than that of the horizontal beam in the vertical plane (yoz plane).

Exemplarily, FIG. 22 is a three-dimensional beam of electromagnetic waves radiated by another antenna 02 provided in the embodiment of the present application in the first radiation mode (that is, the inverted F radiation mode, and the switch 3 is in the off state) and the antenna 02 in the second radiation mode. mode (that is, the dipole radiation mode, the switch 3 is in the ON state) of the comparison diagram of the three-dimensional beam of the electromagnetic wave radiated (that is, the comparison diagram of the three-dimensional pattern of the beam). Fig. 23 is a comparison diagram of the two-dimensional beam of electromagnetic waves radiated by another antenna 02 in the first radiation mode and the two-dimensional beam of electromagnetic waves radiated by the antenna 02 in the second radiation mode provided by the embodiment of the present application (that is, the beam A comparison chart of the two-dimensional pattern of ). 22 and 23 correspond to the case where the inverted F structure 11 , the second radiation structure 2 and the first transmission line 4 are located on the left side of the circuit board 12 . When the inverted F structure 11, the second radiation structure 2 and the first transmission line 4 are located on the left side of the circuit board 12, the beam radiated by the antenna 02 in the first radiation mode is a vertical beam, and the antenna 02 is in the second radiation mode. The radiated beam is a horizontal beam. In Fig. 22, beam b1, beam b2 and beam b3 are beams (vertical beams) radiated by antenna 02 in the first radiation mode, and beam b4, beam b5 and beam b6 are all beams radiated by antenna 02 in the second radiation mode Beams (horizontal beams), beam b1 and beam b4 correspond to the working frequency of 5.1GHz, beam b2 and beam b5 correspond to the working frequency of 5.5GHz, beam b3 and beam b6 correspond to the working frequency of 5.8 GHz. In FIG. 23, each of the comparative case b1, the comparative case b2, and the comparative case b3 is the beam (vertical beam) radiated by the antenna 02 in the first radiation mode and the beam radiated by the antenna 02 in the second radiation mode (horizontal beam) contrast in the horizontal plane (xoz plane). In each of the comparative case b4, the comparative case b5 and the comparative case b6, the beam (vertical beam) radiated by the antenna 02 in the first radiation mode and the beam (horizontal beam) radiated by the antenna 02 in the second radiation mode Contrast in the vertical plane (yoz plane). The operating frequencies corresponding to comparative case b1 and comparative case b4 are both 5.1GHz, the corresponding operating frequencies of comparative case b2 and comparative case b5 are both 5.5GHz, and the corresponding operating frequencies of comparative case b3 and comparative case b6 are both 5.8GHz . The beams in FIG. 22 are three-dimensional beams, the beams in FIG. 23 are two-dimensional beams, and each two-dimensional beam in FIG. 23 is a corresponding three-dimensional beam in FIG. 22 in a corresponding plane. For example, the vertical beam shown by the black solid line in the comparative case b1 in Figure 23 is the beam in the horizontal plane (xoz plane) of the beam b1 in Figure 22, and the horizontal beam shown by the black dotted line in the comparative case b1 in Figure 23 is the beam in the horizontal plane (xoz plane) of beam b4 in FIG. 22 . For another example, the vertical beam shown by the black solid line in the comparative case b4 in Fig. 23 is the beam in the vertical plane (yoz plane) of the beam b1 in Fig. 22, and the black dotted line in the comparative case b4 in Fig. 23 shows The horizontal beam is the beam b4 in FIG. 22 within the vertical plane (yoz plane). Wherein, the working frequency point corresponding to any comparison situation refers to the working frequency point corresponding to the beam shown in the comparison situation. The working frequency point corresponding to any beam refers to the working frequency point of the antenna, and the beam is the beam radiated by the antenna working at the working frequency point. For example, beam b1 is a vertical beam radiated by antenna 02 working at 5.1 GHz. It can be seen from Figure 22 and Figure 23 that the gain of the vertical beam (the beam radiated by the antenna 02 in the first radiation mode) is quite different from the gain of the horizontal beam (the beam radiated by the antenna 02 in the second radiation mode), The difference between the characteristics of the vertical beam and the characteristics of the horizontal beam is more obvious. It can be seen from Figure 23 that the leftward gain of the horizontal beam in the horizontal plane (xoz plane) (the direction from the origin to -90 degrees in the various direction diagrams of the horizontal plane in Figure 23 is the leftward direction) is higher than that of the vertical beam The leftward gain, the rightward gain of the horizontal beam (the direction from the origin to 90 degrees in each direction diagram of the horizontal plane of Figure 23 is the rightward direction) is lower than the rightward gain of the vertical beam, so in the horizontal plane, the horizontal beam and the vertical The beams exhibit complementary properties. In the horizontal plane, the leftward gain of the horizontal beam is 4.4dB to 5.1dB higher than the leftward gain of the vertical beam (4.4dB≈3.464dB-(-0.9429)dB=4.4069dB, 3.464dB is A in the comparative case b1 of Figure 23 Point gain, -0.9429 is the gain of point C in the comparative situation b1 of Figure 23; 5.1dB≈2.964dB-(-2.087)dB=5.051dB, 2.964dB is the gain of point A in the comparative situation b3 of Figure 23 , -2.087 is the gain of point C in the comparative case b3 of Figure 23), the rightward gain of the vertical beam is 6.6dB to 8.7dB higher than the rightward gain of the horizontal beam in the horizontal plane (6.6dB≈(-3.63)dB- (-10.26)dB=6.63dB,-3.63 is the gain of point D in the comparative situation b1 of Figure 23, and-10.26 is the gain of the B point in the comparative situation b1 of Figure 23; 8.7dB≈(-1.412)dB- (-10.09)dB=8.678dB, -1.412 is the gain of point D in the comparative case b3 of Fig. 23, -10.09 is the gain of point B in the comparative case b3 of Fig. 23). In the vertical plane (yoz plane), the upward gain of the vertical beam (the direction from the origin to 0 degree in each direction diagram of the vertical plane in Figure 23 is the upward direction) is 4.4dB to 10dB higher than the upward gain of the horizontal beam (4.4dB ≈(-1.492)dB-(-5.851)dB=4.359dB, -1.492 is the gain of point C in the comparative case b4 of Figure 23, and -5.851 is the gain of point A in the comparative case b4 of Figure 23; 10dB≈ 3.103dB-(-6.942)dB=10.045dB, 3.103 is the gain of point C in the comparative case b6 of Figure 23, -6.942 is the gain of point A in the comparative case b6 of Figure 23), the vertical beam in the vertical plane The downward gain of the beam (the direction from the origin to 180 degrees in each direction diagram of the vertical plane in Figure 23 is the downward direction) is 6.1dB to 8.5dB higher than the downward gain of the horizontal beam (6.1dB≈1.597dB-(- 4.526) dB=6.123dB, 1.597 is the gain of D point in the comparative situation b4 of Fig. 23, and -4.526 is the gain of the B point in the comparative situation b4 of Fig. 23; 8.5dB≈0.7418dB-(-7.7589)dB= 8.5007dB, 0.7418 is the gain of point D in the comparative case b6 of FIG. 23, and -7.7589 is the gain of point B in the comparative case b6 of FIG. 23).

In order to illustrate the radiation effect of the antenna 02 provided in the embodiment of the present application, technicians tested the radiation effect of the antenna 02 provided in the embodiment of the present application and the radiation effect of a conventional dipole antenna in the frequency band of 5 GHz to 6 GHz. The embodiment of the present application also provides comparison diagrams between the radiation effect of the antenna 02 and the radiation effect of a conventional dipole antenna, please refer to FIG. 24 to FIG. 26 for details. Wherein, the antenna 02 corresponding to FIG. 24 to FIG. 26 is an antenna in which the inverted F structure 11, the second radiation structure 2 and the first transmission line 4 are all located on the side where the top edge of the circuit board 12 is located (that is, the antenna 02 shown in FIG. 7 ) . For the case where the inverted F structure 11, the second radiating structure 2 and the first transmission line 4 are all located on the side where the top edge of the circuit board 12 is located, the radiated beam is a horizontal beam when the antenna 02 is in the first radiation mode, and the antenna 02 is in the second radiation mode. The beam radiated in mode is a vertical beam. Wherein, the beam radiated by the conventional dipole antenna is a vertical beam.

As an example, FIG. 24 is a comparison diagram between the radiation efficiency of an antenna 02 provided in the embodiment of the present application and the radiation efficiency of a conventional dipole antenna. It can be seen from FIG. 24 that the radiation efficiency of the antenna 02 is between 50% and 70% in the 5GHz-6GHz frequency band. The radiation efficiency of the antenna 02 in the first radiation mode is basically above 60%. The radiation efficiency of antenna 02 in the second radiation mode is on average 5% lower than that of a conventional dipole antenna. Generally, the radiation efficiency of an antenna without a switch is greater than 60% in the 5GHz to 6GHz frequency band, and the insertion loss of the switch (here refers to the PIN diode) is about 0.5dB. Considering the insertion loss of the switch, the antenna with a switch has an The radiation efficiency of the frequency band is expected to be between 50% and 60%. The radiation efficiency of the antenna 02 including the switch 3 provided in the embodiment of the present application is between 50% and 70% in the frequency range of 5GHz to 6GHz, which is in line with the expected radiation efficiency (the expected radiation efficiency is 50% to 60%).

As an example, FIG. 25 is a comparison diagram of a three-dimensional beam of electromagnetic waves radiated by an antenna 02 provided in an embodiment of the present application and a three-dimensional beam of electromagnetic waves radiated by a conventional dipole antenna. FIG. 26 is a comparison diagram of a two-dimensional beam of electromagnetic waves radiated by an antenna 02 provided in an embodiment of the present application and a two-dimensional beam of electromagnetic waves radiated by a conventional dipole antenna. In Fig. 25, beam c1, beam c2 and beam c3 are all beams (horizontal beams) radiated by antenna 02 in the first radiation mode, and beam c4, beam c5 and beam c6 are all beams radiated by antenna 02 in the second radiation mode beams (vertical beams), beams c7, beams c8 and beams c9 are all beams (vertical beams) radiated by conventional dipole antennas, beams c1, beams c4 and beams c7 correspond to operating frequencies of 5.1GHz, and beams c2 The working frequency points corresponding to beam c5 and beam c8 are all 5.5 GHz, and the working frequency points corresponding to beam c3, beam c6 and beam c9 are all 5.8 GHz. In FIG. 26, each of the comparative case c1, the comparative case c2, and the comparative case c3 is the beam (horizontal beam) radiated by the antenna 02 in the first radiation mode, the beam radiated by the antenna 02 in the second radiation mode (vertical beam) and the beam (vertical beam) radiated by a conventional dipole antenna in the horizontal plane (xoz plane). Each of comparative case c4, comparative case c5, and comparative case c6 is a beam (horizontal beam) radiated by antenna 02 in the first radiation mode, a beam (vertical beam) radiated by antenna 02 in the second radiation mode, and Comparison of beams (vertical beams) radiated by conventional dipole antennas in the xoy plane (vertical plane). Each of comparative case c7, comparative case c8, and comparative case c9 is a beam (horizontal beam) radiated by antenna 02 in the first radiation mode, a beam (vertical beam) radiated by antenna 02 in the second radiation mode, and Comparison of beams (vertical beams) radiated by conventional dipole antennas in the yoz plane (vertical plane). The operating frequency points corresponding to the comparative situation c1, the comparative situation c4 and the comparative situation c7 are all 5.1GHz, the corresponding working frequency points of the comparative situation c2, the comparative situation c5 and the comparative situation c8 are all 5.5GHz, and the comparative situation c3, the comparative situation c6 and the comparative situation In contrast, the corresponding working frequency of c9 is 5.8GHz. The beams in FIG. 25 are three-dimensional beams, and the beams in FIG. 26 are two-dimensional beams. Each two-dimensional beam in FIG. 26 is a corresponding three-dimensional beam in FIG. 25 in a corresponding plane. It can be seen from Fig. 25 and Fig. 26 that the gain of the horizontal beam (the beam radiated by antenna 02 in the first radiation mode) is the same as that of the vertical beam (including the beam radiated by antenna 02 in the second radiation mode and the radiation of the conventional dipole antenna) The difference in the gain of the beam) is relatively large, and the difference between the characteristics of the horizontal beam and the characteristics of the vertical beam is obvious. It can be seen from Figure 26 that the difference between the horizontal beam and the vertical beam corresponding to 5.8GHz is smaller than the difference between the horizontal beam and the vertical beam corresponding to 5.1GHz (compared to the curve of the horizontal beam and the vertical beam corresponding to 5.1GHz, The curve of the horizontal beam corresponding to 5.8GHz is closer to the curve of the vertical beam), and the difference between the horizontal beam and the vertical beam corresponding to 5.8GHz is smaller than the difference between the horizontal beam and the vertical beam corresponding to 5.5GHz (compared to 5.5GHz The curve of the corresponding horizontal beam and the curve of the vertical beam, the distance between the curve of the horizontal beam and the curve of the vertical beam corresponding to 5.8GHz is closer). The difference between the horizontal beam (the beam radiated by the antenna 02 in the first radiation mode) and the vertical beam (including the beam radiated by the antenna 02 in the second radiation mode and the beam radiated by the conventional dipole antenna) is obvious. Before and after the horizontal beam appears in the horizontal plane (xoz plane) (in each direction diagram of the horizontal plane in Figure 26, the direction from the origin to 0 degrees is the forward direction, and the direction from the origin to 180 degrees is the backward direction) orientation, Through the calculation of the curves of the horizontal beam and the curves of the vertical beam in each pattern of the horizontal plane in Fig. 26, it can be obtained that the front and rear gains of the horizontal beam are about 6dB-10dB higher than the front and rear gains of the vertical beam. Can be calculated by the curve of the horizontal beam and the curve of the vertical beam in each direction diagram of the vertical plane (comprising the xoy plane and the yoz plane) in Figure 26: the upward gain of the vertical beam in the vertical plane (the vertical plane of Figure 26 The direction from the origin to 0 degree in each pattern is the upward direction) which is about 6dB-10dB higher than the upward gain of the horizontal beam. By calculating the curve of the vertical beam radiated by antenna 02 in Figure 26 and the curve of the vertical beam radiated by the conventional dipole antenna, it can be obtained: In the high frequency band (5.5GHz-6GHz frequency band), the gain ratio of the vertical beam radiated by antenna 02 The gain of the vertical beam radiated by a conventional dipole antenna is about 1 dB lower. There are two main reasons why the gain of the vertical beam radiated by the antenna 02 is about 1 dB lower than the gain of the vertical beam radiated by the conventional dipole antenna. One reason is that the antenna 02 includes the matching component 112 , and the guiding effect of the matching component 112 broadens the vertical beam radiated by the antenna 02 , so that the directivity of the vertical beam is weakened. Another reason is that the insertion loss of switch 3 reduces the maximum gain of the vertical beam. From Figure 25 and Figure 26, compared with the conventional dipole antenna, the gain of antenna 02 in the horizontal plane is greater than the loss in the vertical plane, and the antenna 02 can perform beam reconstruction, and the multiple-input multiple output (multiple-input In multiple-output, MIMO) communication scenarios, the comprehensive improvement of flat-layer beam coverage and jump-layer beam coverage can be obtained.

To sum up, the antenna provided by the embodiment of the present application can control the antenna to switch between the first radiation mode and the second radiation mode through a switch, thereby controlling the antenna to alternately radiate electromagnetic waves in the first plane and the second plane, because The antenna can radiate electromagnetic waves on the first plane, and can also radiate electromagnetic waves on the second plane, so the beam of the electromagnetic wave radiated by the antenna can realize beam reconstruction, so that the beam coverage of the antenna can be adjusted according to the home environment, the location of the STA, etc. (For example, controlling the antenna to be in the first radiation mode or the second radiation mode according to the home environment, the location of the STA, etc., so as to achieve horizontal beam coverage or vertical beam coverage), the antenna can be applied to communication scenarios in multi-storey houses. The antenna has high radiation efficiency while realizing beam reconfiguration. The antennas provided in the embodiments of the present application can be used for beam coverage requirements of different communication scenarios, and are more adaptable to development requirements.

Based on the same inventive concept, an embodiment of the present application further provides a communication device, where the communication device includes the antenna 02 provided in the embodiment of the present application. The communication device may be a wireless router, ONT, base station, terminal device, etc.

The communication device may also include structures common to general communication devices, for example, including a processor, a memory, and the like. in,

The processor can be a general-purpose processor or a special-purpose processor, and the general-purpose processor can be a central processing unit (central processing unit, CPU). circuit (application-specific integrated circuit, ASIC), field-programmable gate array (field-programmable gate array, FPGA), etc.

In this application, words such as "first", "second", and "third" are used to distinguish the same or similar items with basically the same function and effect. Those skilled in the art can understand that words such as "first", "second", and "third" do not limit the quantity, and cannot be interpreted as indicating or implying relative importance.

In the corresponding embodiments provided in this application, it should be understood that the disclosed antenna, communication device, etc. may be implemented in other configurations. For example, the device embodiments described above are illustrative only.

The above is only an exemplary embodiment of the application, but the protection scope of the application is not limited thereto. Any person familiar with the technical field can easily think of various equivalents within the technical scope disclosed in the application. The modifications or replacements should be covered by the scope of protection of this application. Therefore, the protection scope of the present application should be based on the protection scope of the claims.

Claims (18)

1. An antenna (02), characterized in that the antenna (02) comprises:

   A first radiating structure (1), a second radiating structure (2) and a switch (3);

   The first radiating structure (1) includes an inverted F structure (11) and a circuit board (12), the circuit board (12) is electrically connected to the inverted F structure (11) through a radio frequency signal port, and the second The radiating structure (2) includes a dipole (21), the second radiating structure (2) is electrically connected to the first radiating structure (1) through a first transmission line (4), and the switches (3) are respectively connected to The first transmission line (4) is electrically connected to the first radiation structure (1);

   When the switch (3) is in the first state, the inverted F structure (11) is used to excite the circuit board (12) to radiate in the first plane through the radio frequency signal transmitted to the inverted F structure (11) electromagnetic waves;

   When the switch (3) is in the second state, the first transmission line (4) is used to transmit the radio frequency signal in the inverted F structure (11) to the second radiating structure (2), to excite all The dipole (21) radiates electromagnetic waves on the second plane.
2. The antenna (02) according to claim 1, characterized in that,

   The inverted F structure (11) includes a second transmission line (111) and two matching components (112), the two matching components (112) are arranged on both sides of the second transmission line (111), the two two matching components (112) are respectively electrically connected to the second transmission line (111);

   The circuit board (12) is electrically connected to the inverted F structure (11) through a radio frequency signal port, comprising: the circuit board (12) is electrically connected to the second transmission line (111) through the radio frequency signal port.
3. The antenna (02) according to claim 2, characterized in that,

   The second transmission line (111) includes a first feeding part (1111) and a second feeding part (1112), and the first feeding part (1111) and the second feeding part (1112) are located in parallel in the two planes of

   The two matching components (112) are arranged on both sides of the second transmission line (111), including: the two matching components (112) are arranged on both sides of the first power feeding part (1111);

   The circuit board (12) is electrically connected to the second transmission line (111) through the radio frequency signal port, including: the circuit board (12) is connected to the first power feeding part (1111) through the radio frequency signal port ) and the second power feeding part (1112) are electrically connected.
4. The antenna (02) according to claim 3, characterized in that,

   The matching component (112) includes a first matching branch (1121) and a second matching branch (1122), one end of the first matching branch (1121) is electrically connected to the middle of the second matching branch (1122), The other end of the first matching stub (1121) is grounded;

   The two matching components (112) are respectively electrically connected to the second transmission line (111), including: one end of the second matching stub (1122) of each matching component (112) is connected to the first The power feeding part (1111) is electrically connected.
5. The antenna (02) according to claim 4, characterized in that,

   The difference in the distance between the first matching stub (1121) of the two matching components (112) and the first power feeding part (1111) is smaller than a first difference threshold, and the two matching components The difference between the lengths of the second matching stubs (1122) of (112) is smaller than a second difference threshold, and the second matching stubs (1122) of the two matching components (112) are different from the first feeder The projected length of the distance between the connection positions of the electrical parts (1111) in a first direction is smaller than a first distance threshold, and the first direction is parallel to the length direction of the first transmission line (4).
6. The antenna (02) according to claim 4 or 5, characterized in that,

   The length range of the first matching stub (1121) is (0, λ/4), where λ is the working wavelength of the electromagnetic wave radiated by the antenna (02).
7. The antenna (02) according to any one of claims 1 to 6, characterized in that,

   The first transmission line (4) includes a third feeder (41) and a fourth feeder (42), the third feeder (41) and the fourth feeder (42) are located in parallel in the two planes of

   The switch (3) is respectively electrically connected to the first transmission line (4) and the first radiation structure (1), comprising: the switch (3) is respectively connected to the third power feeding part (41) and The inverted F structure (11) is electrically connected.
8. The antenna (02) according to claim 7, characterized in that,

   The switch (3) is electrically connected to the third power feeding part (41) and the inverted F structure (11) respectively, comprising: the third power feeding part (41) and the inverted F structure (11 ) with a gap, and the switch (3) is connected across the gap.
9. The antenna (02) according to any one of claims 1 to 8, characterized in that,

   The number of the switch (3) is one.
10. The antenna (02) according to any one of claims 1 to 9, characterized in that,

    The first state is an off state, and the second state is an on state.
11. The antenna (02) according to any one of claims 1 to 10, characterized in that,

    The dipole (21) includes a first radiating arm (211) and a second radiating arm (212), and the second transmission line (111) in the inverted-F structure (11) includes a first feeding part (1111) and a second feeder (1112), the first transmission line (4) includes a third feeder (41) and a fourth feeder (42);

    The second radiating structure (2) is electrically connected to the first radiating structure (1) through a first transmission line (4), including:

    One end of the first radiating arm (211) close to the second radiating arm (212) is electrically connected to one end of the third feeding part (41), and the other end of the third feeding part (41) electrically connected to the first power feeding part (1111) through the switch (3);

    One end of the second radiating arm (212) close to the first radiating arm (211) is electrically connected to the fourth feeding part (42), and the other end of the fourth feeding part (42) is connected to the The second power feeding part (1112) is electrically connected.
12. The antenna (02) according to claim 11, characterized in that,

    The width of the first power feeding part (1111) is larger than the width of the third power feeding part (41), and the width of the second power feeding part (1112) is larger than that of the fourth power feeding part (42). width.
13. The antenna (02) according to claim 11 or 12, characterized in that the antenna further comprises: a carrier substrate (5), the first radiating structure (1) and the second radiating structure (2) respectively printed on said carrier substrate (5).
14. The antenna (02) according to claim 13, characterized in that,

    The matching components (112) in the first radiating arm (211), the third feeding part (41), the first feeding part (1111) and the inverted F structure (11) are respectively printed on one surface of the carrier substrate (5);

    The second radiating arm (212), the fourth power feeding part (42) and the second power feeding part (1112) are respectively printed on the other board surface of the carrier substrate (5).
15. The antenna (02) according to claim 14, characterized in that,

    The orthographic projection of the first axis of the first power feeding part (1111) in the reference plane, the orthographic projection of the first axis of the second power feeding part (1112) in the reference plane, the third The orthographic projection of the first axis of the feeder (41) in the reference plane and the orthographic projection of the first axis of the fourth feeder (42) in the reference plane are collinear;

    Any one of the first power feeder (1111), the second power feeder (1112), the third power feeder (41) and the fourth power feeder (42) The first axis of the reference plane is parallel to the length direction of the feeding part, and the reference plane is parallel to the board surface of the carrier substrate (5).
16. The antenna (02) according to any one of claims 1 to 15, characterized in that,

    The circuit board (12) is electrically connected to the inverted F structure (11) through a radio frequency signal port, including: the circuit board (12) is electrically connected to a radio frequency signal line (6) through a radio frequency signal port, and the radio frequency signal The wire (6) is electrically connected with the inverted F structure (11).
17. The antenna (02) according to any one of claims 1 to 16, characterized in that,

    said first plane is a horizontal plane and said second plane is a vertical plane; or,

    The first plane is a vertical plane, and the second plane is a horizontal plane.
18. A communication device, characterized by comprising the antenna (02) according to any one of claims 1 to 17.

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