WO2022242014A1 - 基于超表面的双极化宽带毫米波滤波天线及通信设备 - Google Patents

基于超表面的双极化宽带毫米波滤波天线及通信设备 Download PDF

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WO2022242014A1
WO2022242014A1 PCT/CN2021/123017 CN2021123017W WO2022242014A1 WO 2022242014 A1 WO2022242014 A1 WO 2022242014A1 CN 2021123017 W CN2021123017 W CN 2021123017W WO 2022242014 A1 WO2022242014 A1 WO 2022242014A1
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metal
dual
wave filter
antenna
polarized broadband
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PCT/CN2021/123017
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English (en)
French (fr)
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薛泉
杨琬琛
车文荃
黄婧
刘洽广
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华南理工大学
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Publication of WO2022242014A1 publication Critical patent/WO2022242014A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H01Q15/0086—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices having materials with a synthesized negative refractive index, e.g. metamaterials or left-handed materials
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Definitions

  • the invention relates to the field of antennas, in particular to a metasurface-based dual-polarization broadband millimeter-wave filter antenna and communication equipment.
  • Massive MIMO antenna technology has become a key technology of 5G.
  • the antenna system is developing in the direction of miniaturization, low power consumption, and multi-band.
  • Antennas and filters are very important passive components in the front end of RF systems, and performance design is particularly important.
  • the traditional design of directly using matching devices or matching networks to cascade filters and antennas not only increases the overall size of the system, but also increases insertion loss. , which seriously deteriorates the overall efficiency of the system, and this problem is more prominent in the 5G antenna system.
  • 5G antenna arrays using Massive MIMO technology face the design challenges of inter-array decoupling and miniaturization. Because of the coupling problem between the antenna sub-arrays in different frequency bands, the radiation pattern of the antenna array is seriously affected, and the performance of the array is deteriorated.
  • the method of loading a duplexer or a decoupling network not only increases the loss, but also increases the overall size, which is not conducive to system integration.
  • the filter antenna can achieve a better out-of-band suppression effect outside the pass-band of the antenna, and achieve a better isolation effect between antennas working in different frequency bands. Therefore, the array composed of filter antenna elements not only reduces the loss, but also meets the needs of system miniaturization, which is of great significance to the decoupling of the millimeter wave frequency band of 5G communication.
  • the filter antenna design of "integrated antenna in package" that can be applied to millimeter wave and higher frequency bands can be one of the methods to solve this problem.
  • the primary purpose of the present invention is to provide a metasurface-based dual-polarization broadband millimeter-wave filter antenna.
  • the antenna can achieve higher gain and better filtering performance in the millimeter wave frequency band.
  • a secondary object of the present invention is to provide a communication device.
  • the metasurface-based dual-polarized wideband millimeter-wave filter antenna includes two layers of superimposed dielectric substrates, the upper and lower surfaces of the lower dielectric substrate are respectively provided with an upper metal floor and a lower metal floor, and the upper surface of the upper dielectric substrate is provided with
  • the metasurface structure includes N metal patches arranged in an array, each metal patch has a slit etched on it, the upper dielectric substrate is connected to the upper metal floor, and the upper metal floor etches a Jerusalem cross slit.
  • grounding metal branch is arranged under the metal patch and located on the upper dielectric substrate, one end of the metal grounding post is connected to the grounding metal branch, and the other end is connected to the upper metal floor .
  • the metasurface structure forms an included angle of 45 degrees with the Jerusalem cross gap.
  • the metasurface structure includes four metal patches, and two L-shaped slits are etched on each metal patch, and the two L-shaped slits are symmetrical about the diagonal line of the metal patch, and are respectively adjacent to the metal patch. The sides are vertical.
  • the loading of the L-shaped slit shifts the high-order mode of the metasurface structure to low frequency, improves the roll-off of the edge of the passband, and introduces a high-frequency second zero point to improve the high-frequency out-of-band suppression level.
  • the arrangement directions of the grounding metal branches and the metal grounding posts are at an angle of 45 degrees to the Jerusalem cross gap.
  • it also includes two coplanar metal strip feeders, which are located directly below the Jerusalem cross gap, and the orthogonality of the two metal strip feeders is realized through a metal bridge of a short strip line.
  • an isolation structure is adopted around the gap between the metal ribbon feeder and the Jerusalem cross.
  • the distance between adjacent metal patches is 0.01 ⁇ g0 ⁇ 0.3 ⁇ g0, where ⁇ g0 is the effective wavelength of the medium corresponding to the center frequency of the antenna.
  • a communication device including the dual-polarization broadband millimeter-wave filter antenna.
  • the loaded structure of the present invention includes grounding metal stubs and L-shaped slots. Since there is no additional filter circuit, the volume and additional loss of the radio frequency front end can be effectively reduced, and the antenna has a compact structure.
  • the present invention realizes a wider bandwidth through the filter structure of slot coupling feeding and loading of grounded metal stubs.
  • the present invention enables the antenna to generate multiple radiation zero points in a specific frequency band through metal metasurfaces, loading grounding metal branches, and loading L-shaped gaps, and the stop band part is better suppressed.
  • the present invention adopts multi-layer LTCC low-temperature co-fired ceramic lamination technology, which is structurally integrated, easy to interconnect with back-end communication system components, and can be applied to the multifunctional fusion design of 5G large-scale arrays.
  • Fig. 1 is the three-dimensional structure schematic diagram of the present invention
  • Fig. 2 is an exploded top view of Fig. 1, including the metasurface structure etched with L-shaped slits and the upper metal floor;
  • Fig. 3 is an exploded top view of Fig. 1, including a grounded metal branch, a metal grounding column and an upper metal floor;
  • Figure 4 is an exploded top view of Figure 1, including metal ribbon feeders, metal isolation strips, metal isolation columns, upper metal floors and metal bridges;
  • Fig. 5 is the side view of Fig. 1 of the present invention.
  • Fig. 6 (a) is the S parameter of the present invention: the schematic diagram that reflection coefficient, polarization isolation change with frequency;
  • Fig. 6 (b) is the schematic diagram that the gain of the present invention changes with frequency
  • Fig. 6 (c) is the schematic diagram that the efficiency of the present invention changes with frequency
  • Figure 7(a) is a schematic diagram of the +45° radiation pattern at 28GHz according to the present invention.
  • Figure 7(b) is a schematic diagram of the -45° radiation pattern at 28GHz of the present invention.
  • Fig. 8 (a) is the schematic diagram of contrast antenna 1 of the present invention.
  • Fig. 8 (b) is the schematic diagram of contrast antenna II of the present invention.
  • Figure 8(c) is a schematic diagram of the comparative antenna III of the present invention.
  • Fig. 9 (a) is the schematic diagram that the S parameter of three comparative antennas of the present invention changes with frequency
  • FIG. 9( b ) is a schematic diagram of gain variation with frequency of three comparative antennas of the present invention.
  • a metasurface-based dual-polarized broadband millimeter-wave filter antenna adopts LTCC processing technology, and the thickness of each layer of LTCC dielectric substrate is 0.094mm. It includes two layers of superimposed dielectric substrates, specifically an upper dielectric substrate 3 and a lower dielectric substrate 8, the upper surface of the upper dielectric substrate is provided with a metasurface structure 1, and the upper and lower surfaces of the lower dielectric substrate are respectively provided with an upper metal floor 6 and the lower metal floor 14 , the ground metal branch 4 is arranged in the upper dielectric substrate, and the ground metal branch is connected to the upper metal floor 6 through the metal ground post 5 .
  • the shape of the grounded metal branch is not limited to the elongated branch, and may also be trapezoidal, T-shaped and so on.
  • the upper end of the metal grounding column 5 can be located at any position on the midline of the branch, and the lower end is located on both sides of the Jerusalem cross gap 7 on the upper metal floor 6. ° included angle to get lower passband edge frequency null and improve in-band matching
  • a Jerusalem cross slit 7 is etched on the upper metal floor 6 , and the midpoint of the Jerusalem cross slit is located at the center of the upper metal floor.
  • Two coplanar metal strip feeders 9 and 10 are set directly below the Jerusalem cross gap. In order to avoid crossing, the crossing of the two feeders is realized through a metal bridge 11 with two through holes and a short strip line of.
  • a metal isolation strip 12 and several metal isolation columns 13 are used to form an isolation structure around the metal ribbon feeders 9, 10 and the Jerusalem cross gap 7, so as to avoid the diffusion of the feed signal.
  • the metasurface structure includes N metal patches arranged in an array, and the metal patches are rectangular patches.
  • N is 4, arranged in a 2*2 array, four metal patches are arranged at equal intervals, and the center point is the center of the upper dielectric substrate.
  • the arrangement of the metasurface structure is at an angle of 45° with the Jerusalem cross slit 7, so as to obtain the first zero point of the sideband on the passband; two L-shaped slits 2 are etched on each metal patch, and the shape of the slits can be changed, or It can be straight, U-shaped, etc.
  • Two L-shaped slits are distributed symmetrically along the diagonal, as shown in Figure 2, and are respectively perpendicular to the adjacent sides of the metal patch to obtain the second zero point of the upper side frequency of the passband.
  • the adjacent sides may be adjacent sides on the inner edge close to the center point of the upper medium base, or adjacent sides on the outer edge far away from the center point.
  • grounding metal branches 4 which are located directly below the metal patch.
  • the grounding metal branches are rectangular and connected to the upper metal floor 6 through the metal grounding column 5.
  • the lower end of the metal grounding column 5 is located on the upper metal floor. 6.
  • the metal grounding posts are four, which are arranged symmetrically close to the center of the antenna.
  • the arrangement direction of the grounding metal branches 4 and the metal grounding posts 5 forms an angle of 45° with the Jerusalem cross gap 7. , to get the lower passband side frequency zero and improve the in-band matching.
  • the dielectric constant ⁇ r of the upper and lower dielectric substrates is 2 to 7
  • the dielectric substrate and the metal floor are both square and the side length g is 0.2 ⁇ to 1.5 ⁇ , where ⁇ is the free space wavelength corresponding to the center frequency .
  • the length of both sides of the metal floor can be selected within the above range according to the size requirements of the antenna, and the filter function of stop band suppression can be realized.
  • the distance h 1 between the metasurface structure and the upper metal floor is 0.05 ⁇ ⁇ 0.2 ⁇ , where ⁇ is the free space wavelength corresponding to the center frequency.
  • the distance between the metasurface structure and the upper metal floor can be selected within the above-mentioned range according to the bandwidth requirements of the antenna and the processing realization ability, and the filter function of stopband suppression can be realized.
  • the distance h 2 between the grounded metal branch and the upper metal floor is 0.008 ⁇ ⁇ 0.15 ⁇ , where ⁇ is the free space wavelength corresponding to the center frequency.
  • the distance between the grounded metal branch and the upper metal floor can be selected within the above range according to the bandwidth requirements of the antenna, and the filter function of stop band suppression can be realized.
  • the distance h 3 between the upper metal floor and the lower metal floor is 0.05 ⁇ ⁇ 0.15 ⁇ , where ⁇ is the free space wavelength corresponding to the center frequency.
  • the distance between the upper metal floor and the lower metal floor can be selected within the above range according to the bandwidth requirements of the antenna, and the filter function of stop band suppression can be realized.
  • the side length b of the metal patch is 0.2 ⁇ g0 ⁇ 0.7 ⁇ g0, where ⁇ g0 is the effective wavelength of the medium corresponding to the center frequency of the antenna.
  • the side length of the metal patch can be used to adjust the impedance matching in the passband and the first zero frequency of the sideband on the passband.
  • the side length is determined by the thickness of the dielectric substrate, the dielectric constant and the distance between the metal metasurface patch and the upper metal floor , the filter function of stopband suppression can be realized within the above range.
  • the distance bp between adjacent metal patches in the metasurface structure is 0.01 ⁇ g0 ⁇ 0.3 ⁇ g0, where ⁇ g0 is the effective wavelength of the medium corresponding to the center frequency of the antenna.
  • the metal patch spacing can be used to adjust the impedance matching in the passband, the first zero frequency of the passband upper side frequency and the upper stopband suppression performance.
  • the spacing is determined by the thickness of the dielectric substrate, the dielectric constant and the metal metasurface patch and the upper metal floor. The spacing is determined, and the filter function of stopband suppression can be realized within the above range.
  • the slot position ds etched on the outer edge of the metal patch is 0.02 ⁇ g0-0.68 ⁇ g0
  • the slot lengths l 1 and l 2 are 0.02 ⁇ g0-0.68 ⁇ g0, where ⁇ g0 is the effective wavelength of the medium corresponding to the antenna center frequency.
  • the position and length of the gap can be used to adjust the impedance matching in the passband, the second zero frequency of the upper sideband of the passband and the suppression performance of the upper stopband.
  • the position and length of the gap are determined by the thickness of the dielectric substrate, the dielectric constant and the metal metasurface patch The distance from the upper metal floor is determined, and the filter function of stop band suppression can be realized within the above range.
  • the length l4 of the grounded metal stub is 0.02 ⁇ g0-0.36 ⁇ g0 and the width l3 is 0.02 ⁇ g0-0.18 ⁇ g0 , where ⁇ g0 is the effective wavelength of the medium corresponding to the center frequency of the antenna.
  • the length and width of the grounded metal stub are used to adjust the impedance matching in the passband, the zero frequency of the lower side frequency of the passband and the suppression performance of the lower stopband.
  • the grounded metal stub is equivalent to the stop-band effect of the parallel 1/4 ⁇ g0 short-circuit stub, which produces the lower-frequency zero point of the antenna. Its length is mainly determined by the thickness of the dielectric substrate, the dielectric constant and the distance between the grounded metal branch and the upper metal floor, and the filter function of stop band suppression can be realized within the above range.
  • the dielectric constant ⁇ r of the upper and lower dielectric substrates is 5.9; the dielectric substrate and the metal floor are square, and the side length g is 6mm; the distance h between the metasurface structure and the upper metal floor is 0.564mm; The distance h 2 between the grounded metal branch and the upper metal floor is 0.376mm; the distance h 3 between the upper metal floor and the lower metal floor is 0.282mm.
  • ⁇ is the free-space wavelength corresponding to the center frequency
  • ⁇ g 0 is the effective wavelength of the medium corresponding to the center frequency.
  • the value of ⁇ is 11.16 mm
  • the value of ⁇ g 0 is 4.6 mm.
  • the side length b of the metal patch is 1.55mm
  • the pitch bp of the metal patch is 0.35mm
  • the width s of the L-shaped slit is 0.1mm
  • the distance ds between the slit and the edge of the patch is 0.75mm.
  • the slit length l 1 is 0.6mm
  • l 2 is 0.2mm.
  • the length l 3 of the grounded metal stub is 0.42 mm and the width l 4 is 0.28 mm, the center distance d of the metal ground post is 1.2 mm and the diameter r is 0.2 mm.
  • the length f 1 of the middle part of the Jerusalem cross slit etched on the floor is 1.3 mm, the length f 2 of the slit at both ends is 0.8 mm, and the width fw is 0.1 mm; the diameter of the metal column used to connect the cross-layer feeder in the metal bridge r1 is 0.1mm.
  • the metasurface-based dual-polarized broadband millimeter-wave filter antenna of this embodiment has a relatively high stable gain in the working frequency band, with an average gain of 5.8dBi and a maximum gain of 6.1dBi , the passband radiation efficiency is higher than 90%, and has good frequency selectivity at the edge of the working frequency band, the low-frequency out-of-band suppression is 15dB, the high-frequency out-of-band suppression is 30dB, and the stopband efficiency is lower than 5%.
  • the antenna is well matched at the center frequency, has a wide impedance bandwidth, the bandwidth is 19.5%, the in-band polarization isolation is greater than 25dB, and completely covers the 5G communication millimeter wave frequency band.
  • the metasurface-based dual-polarized broadband millimeter-wave filter antenna of this embodiment has a good pattern symmetry in the passband, and the cross-polarization level is -30dB the following.
  • the metasurface-based dual-polarization wideband millimeter-wave filter antenna provided by the embodiment of the present invention uses a Jerusalem cross slit to couple and excite the metal metasurface, and generates transmission zero points and Additional resonant points in the passband to achieve wideband antennas with filtered response.
  • the grounded metal stub in this embodiment is equivalent to the stop band effect of the parallel quarter short-circuit stub, which produces the lower sideband zero point of the antenna; the metal metasurface and the L-shaped slit etched on the metasurface patch
  • the reverse current distribution can be realized on the patch, the upper sideband zero point of the antenna is generated, and the filter response is realized, the sideband has better selectivity, and the stopband suppression is good.
  • antennas shown in Figure 8(a)-8(c) are added for comparison, such as antenna I in Figure 8(a), antenna I only includes the metasurface structure 1 fed by slot coupling;
  • antenna II shown in (b) is based on the antenna I, and the ground metal branch 4 and the metal ground post 5 are added under the metasurface structure 1;
  • the antenna III in Figure 8(c) is based on the antenna II, and the supersurface An L-shaped gap 2 is added to the surface structure 1 .
  • the antenna Since the antenna has no additional filter/resonator or filter circuit, the volume of the RF front-end can be greatly reduced, and there is no additional insertion loss; in addition, the introduction of the filter structure adds capacitive and inductive resonance, which will also affect the antenna. Impedance, which introduces a resonance point in the passband, broadens the antenna bandwidth, and can achieve filtering performance in a compact and high-gain structure.
  • the antenna has a simple structure, can realize ⁇ 45° dual-polarization operation under an integrated structure, and has a filter response with high selectivity and high stop-band suppression level, and is suitable for the functional fusion design of 5G millimeter-wave base station antennas.
  • a communication device comprising the metasurface-based dual-polarized broadband millimeter-wave filter antenna described in Embodiment 1.

Abstract

本发明公开了基于超表面的双极化宽带毫米波滤波天线及通信设备，包括两层叠加设置的介质基板，下层介质基板的上表面及下表面分别设置上层金属地板及下层金属地板，所述上层介质基板的上表面设置超表面结构，所述超表面结构包括N个呈阵列排布的金属贴片，每个金属贴片上蚀刻缝隙，所述上层介质基板与上层金属地板相连，上层金属地板蚀刻耶路撒冷十字缝隙。该天线结构简单，可在不增加天线尺寸的情况下同时实现辐射和滤波，大大减少射频前端的体积且没有额外的插入损耗。

Description

基于超表面的双极化宽带毫米波滤波天线及通信设备 技术领域
本发明涉及天线领域，具体涉及基于超表面的双极化宽带毫米波滤波天线及通信设备。
背景技术
随着5G技术的发展应用，大规模多输入多输出(Massive MIMO)天线技术成为5G一项关键技术。为了在有限的空间集成更多的射频收发信道及天线单元实现多频段系统共存，天线系统向小型化、低功耗、多频段的方向发展。天线和滤波器作为射频系统前端非常重要的无源器件，性能设计尤为重要，传统直接利用匹配器件或者匹配网络将滤波器和天线级联的设计不仅增加了系统的整体尺寸，还增加了插入损耗，严重恶化了系统整体效率，这个问题在5G天线系统更加突出。为解决这一问题，国内外的研究学者提出将两个无源器件的功能融合在一个无源器件中，同时实现滤波和辐射两种功能，即滤波天线(filtering antenna/filtenna)。这种方案有效减小了整体尺寸，降低了插入损耗，对提高射频前端系统的整体效率有重要意义。
同时，采用Massive MIMO技术的5G天线阵列面临着阵间去耦和小型化的设计挑战。因为不同频段的天线子阵列之间的耦合问题，严重影响了天线阵列的辐射方向图，恶化阵列性能。而采用加载双工器或者去耦网络的方法，不仅增加了损耗，还增加了整体尺寸不利于系统集成。滤波天线作为一种具有带通效果的无源器件，在天线工作的通带外能实现较好的带外抑制效果，使工作在不同频段的天线之间实现较好的隔离效果。因而采用滤波天线单元组成的阵列不仅降低了损耗，还可以满足系统小型化的需求，对5G通信的毫米波频段异频去耦具有重要意义。
在5G通信的毫米波频段，为了实现系统的多功能、小型化、低功耗，采用三维集成的垂直向封装技术集成多个系统模块已经成为发展趋势。但是在毫米波频段，滤波器Q值太低，不适合集成在芯片中，单独封装也面临互连损耗较大的问题。因此，可应用于毫米波及更高频段的“封装集成天线”的滤波天线设计可成为解决这一问题的方法之一。
发明内容
为了克服现有技术存在的缺点与不足，本发明首要目的是提供一种基于超表面的双极化宽带毫米波滤波天线。该天线能在毫米波频段实现较高的增益以及较好的滤波性能。
本发明的次要目的是提供一种通信设备。
本发明首要目的是采用如下技术方案：
基于超表面的双极化宽带毫米波滤波天线，包括两层叠加设置的介质基板，下层介质基板的上表面及下表面分别设置上层金属地板及下层金属地板，所述上层介质基板的上表面设置超表面结构，所述超表面结构包括N个呈阵列排布的金属贴片，每个金属贴片上蚀刻缝隙，所述上层介质基板与上层金属地板相连，上层金属地板蚀刻耶路撒冷十字缝隙。
进一步，还包括接地金属枝节及金属接地柱，所述接地金属枝节设置在金属贴片的下方，且位于上层介质基板，所述金属接地柱一端与接地金属枝节连接，另一端与上层金属地板连接。
进一步，所述超表面结构与耶路撒冷十字缝隙呈45度夹角。
进一步，所述超表面结构包括四个金属贴片，每个金属贴片上蚀刻两条L型缝隙，两条L型缝隙关于金属贴片对角线对称，且分别与金属贴片的相邻边垂直。
进一步，L型缝隙的加载使超表面结构的高次模式向低频移动，改善通带边缘的滚降性，并且引入高频第二零点，提高高频带外抑制水平。
进一步，所述接地金属枝节和金属接地柱的排布方向均与耶路撒冷十字缝隙呈45度角。
进一步，还包括两条共平面的金属带状馈线，位于耶路撒冷十字缝隙的正下方，两条金属带状馈线正交是通过一条短带状线的金属桥实现。
进一步，所述金属带状馈线和耶路撒冷十字缝隙周围采用隔离结构。
进一步，相邻金属贴片间距为0.01λg0～0.3λg0，其中，λg0为天线中心频率对应的介质有效波长。
本发明次要目的是采用如下技术方案：
一种通信设备，包括所述的双极化宽带毫米波滤波天线。
与现有技术相比，本发明的有益效果如下：
(1)本发明加载的结构包括接地金属枝节、L型缝隙，由于没有额外的滤 波电路，可以有效减小射频前端的体积和额外的损耗，使天线具有紧凑的结构。
(2)本发明通过缝隙耦合馈电、加载接地金属枝节的滤波结构，实现了较宽的带宽。
(3)本发明通过金属超表面、加载接地金属枝节、加载L型缝隙，使天线在特定频段产生多个辐射零点，阻带部分得到较好的抑制水平。
(4)本发明采用多层LTCC低温共烧陶瓷压合技术，结构集成，易于与后端通信系统组件互联，可运用于5G大规模阵列的多功能融合设计。
附图说明
图1是本发明的立体结构示意图；
图2是图1的分解俯视图，包括蚀刻L型缝隙的超表面结构及上层金属地板；
图3是图1的分解俯视图，包括接地金属枝节、金属接地柱及上层金属地板；
图4是图1的分解俯视图，包括金属带状馈线，金属隔离条带，金属隔离柱，上层金属地板及金属桥；
图5是本发明图1的侧视图；
图6(a)是本发明的S参数：反射系数、极化隔离随频率变化的示意图；
图6(b)是本发明的增益随频率变化的示意图；
图6(c)是本发明的效率随频率变化的示意图；
图7(a)是本发明的在28GHz处的+45°辐射方向图示意图；
图7(b)是本发明的在28GHz处的-45°辐射方向图示意图；
图8(a)是本发明对比天线I的示意图；
图8(b)是本发明对比天线II的示意图；
图8(c)是本发明对比天线III的示意图；
图9(a)是本发明的三个对比天线的S参数随频率变化的示意图；
图9(b)是本发明的三个对比天线的增益随频率变化的示意图。
具体实施方式
下面结合实施例及附图，对本发明作进一步地详细说明，但本发明的实施方式不限于此。
实施例1
如图1及图5所示，一种基于超表面的双极化宽带毫米波滤波天线，采用LTCC加工工艺，每层LTCC介质基板厚度是0.094mm。包括两层叠加设置的介质基板，具体为上层介质基板3及下层介质基板8，所述上层介质基板的上表面设置超表面结构1，下层介质基板的上表面及下表面分别设置上层金属地板6及下层金属地板14，所述接地金属枝节4设置在上层介质基板中，所述接地金属枝节通过金属接地柱5与上层金属地板6相连接。
所述接地金属枝节的形状不局限于长条形枝节，也可以是梯形，T形等。
金属接地柱5上端可以位于枝节中线上的任意位置，下端位于上层金属地板6上耶路撒冷十字缝隙7两侧，所述接地金属枝节4和金属接地柱5的排布方向与耶路撒冷十字缝隙7呈45°夹角，以得到通带下边频零点并改善带内匹配
如图4所示，所述上层金属地板6上蚀刻耶路撒冷十字缝隙7，所述耶路撒冷十字缝隙的中点位于上层金属地板的中心位置。在耶鲁撒冷十字缝隙的正下方设置两条共平面的金属带状馈线9、10，为了避免交叉，两条馈线的交叉是通过具有两个通孔和一条短带状线的金属桥11实现的。在所述金属带状馈线9、10和耶路撒冷十字缝隙7周围采用金属隔离条带12和若干个金属隔离柱13形成隔离结构，避免馈电信号的扩散。
所述超表面结构包括N个呈阵列排布的金属贴片，所述金属贴片为矩形贴片。本实施例中，N为4个，呈2*2阵列排布，四个金属贴片等间距排列，中心点为上层介质基板的中心。所述超表面结构的排列方式与耶路撒冷十字缝隙7呈45°夹角，以得到通带上边频第一零点；每个金属贴片上蚀刻两条L型缝隙2，缝隙形状可以变化，也可以是一字型、U型等。两条L形缝隙沿着对角线对称分布，如图2所示，分别垂直于金属贴片相邻边，以得到通带上边频第二零点。相邻边可以是靠近上层介质基中心点的内侧边缘相邻边，也可以是远离中心点的外侧边缘相邻边。
如图3所示，接地金属枝节4共4个，位于金属贴片的正下方，接地金属枝节为矩形，通过金属接地柱5与上层金属地板6相连接，金属接地柱5下端位于上层金属地板6上耶路撒冷十字缝隙7两侧，所述金属接地柱为四个，靠近天线中心点对称设置，所述接地金属枝节4和金属接地柱5的排布方向与耶路撒冷十字缝隙7呈45°夹角，以得到通带下边频零点并改善带内匹配。
进一步地，上、下层介质基板的介电常数ε r为2～7，介质基板、金属地板 均为方形且边长g均为0.2λ～1.5λ，其中，λ为中心频率对应的自由空间波长。金属地板的两边边长可根据天线的尺寸要求在上述范围内自行选择，均可实现阻带抑制的滤波功能。
进一步地，所述超表面结构与上层金属地板之间的间距h 1为0.05λ～0.2λ，其中，λ为中心频率对应的自由空间波长。超表面结构与上层金属地板之间的间距可根据天线的带宽要求、加工实现能力在上述范围内自行选择，均可实现阻带抑制的滤波功能。
进一步地，所述接地金属枝节与上层金属地板之间的间距h 2为0.008λ～0.15λ，λ为中心频率对应的自由空间波长。接地金属枝节与上层金属地板的间距可根据天线的带宽要求在上述范围内自行选择，均可实现阻带抑制的滤波功能。
进一步地，所述上层金属地板与下层金属地板之间的间距h 3为0.05λ～0.15λ，λ为中心频率对应的自由空间波长。上层金属地板与下层金属地板之间的间距可根据天线的带宽要求在上述范围内自行选择，均可实现阻带抑制的滤波功能。
进一步地，所述金属贴片的边长b为0.2λg0～0.7λg0，其中，λg0为天线中心频率对应的介质有效波长。金属贴片的边长可以用于调节通带内阻抗匹配、通带上边频第一零点频率，边长由介质基板的厚度、介电常数及金属超表面贴片与上层金属地板的间距决定，在上述范围内均可实现阻带抑制的滤波功能。
进一步地，所述超表面结构中相邻金属贴片间距bp为0.01λg0～0.3λg0，其中，λg0为天线中心频率对应的介质有效波长。金属贴片间距可以用于调节通带内阻抗匹配、通带上边频第一零点频率和上阻带抑制性能，间距由介质基板的厚度、介电常数及金属超表面贴片与上层金属地板的间距决定，在上述范围内均可实现阻带抑制的滤波功能。
进一步地，所述蚀刻在金属贴片外边缘的缝隙位置ds为0.02λg0～0.68λg0，缝隙长度l 1、l 2为0.02λg0～0.68λg0，其中，λg0为天线中心频率对应的介质有效波长。缝隙的位置和长度可以用于调节通带内阻抗匹配、通带上边频第二零点频率和上阻带抑制性能，缝隙位置和长度由介质基板的厚度、介电常数及金属超表面贴片与上层金属地板的间距决定，在上述范围内均可实现阻带抑制的滤波功能。
进一步地，所述接地金属枝节的长度l 4为0.02λg0～0.36λg0且宽度l 3为0.02λg0～0.18λg0，其中，其中，λg0为天线中心频率对应的介质有效波长。接地金属枝节的长度、宽度用于调整通带内阻抗匹配、通带下边频零点频率和下 阻带抑制性能。接地金属枝节相当于并联式1/4λg0短路短截线阻带效应，产生天线的下边频零点。其长度主要由介质基板的厚度、介电常数及接地金属枝节与上层金属地板的间距决定，在上述范围内均可实现阻带抑制的滤波功能。
本实施例中的具体尺寸如下：
上、下层介质基板的介电常数ε r为5.9；所述介质基板、金属地板为方形，边长g为6mm；所述超表面结构与上层金属地板之间的间距h 1为0.564mm；所述接地金属枝节与上层金属地板之间的间距h 2为0.376mm；所述上层金属地板与下层金属地板之间的间距h 3为0.282mm。其中，λ为中心频率对应的自由空间波长，λg 0为中心频率对应的介质有效波长，本实施例中λ取值为11.16mm，λg 0取值为4.6mm。
所述金属贴片的边长b为1.55mm，所述金属贴片的间距bp为0.35mm，所述L型缝隙宽度s为0.1mm，所述缝隙距离贴片边缘距离ds为0.75mm，所述缝隙长度l 1为0.6mm,l 2为0.2mm。
所述接地金属枝节的长度l 3为0.42mm且宽度l 4为0.28mm，所述金属接地柱的中心距离d为1.2mm且直径r为0.2mm。
所述蚀刻在地板上的耶路撒冷十字缝隙中间部分长度f 1为1.3mm且两端缝隙长度f 2为0.8mm，宽度fw为0.1mm；所述金属桥中用于连接跨层馈线的金属柱直径r 1为0.1mm。
如图6(a)～6(c)所示，本实施例的基于超表面的双极化宽带毫米波滤波天线在工作频段内具有较高的稳定增益，平均增益5.8dBi，最大增益6.1dBi，通带辐射效率高于90％，且在工作频段边缘具有良好的频率选择性，低频带外抑制为15dB，高频带外抑制为30dB，阻带效率低于5％。天线在中心频率处匹配良好，具有较宽的阻抗带宽，带宽为19.5％，带内极化隔离大于25dB，完全覆盖5G通信毫米波频段。
如图7(a)～7(b)所示，本实施例的基于超表面的双极化宽带毫米波滤波天线在通带内的方向图对称性基本良好，交叉极化电平在-30dB以下。
本发明实施例提供的基于超表面的双极化宽带毫米波滤波天线，由耶路撒冷十字缝隙耦合激励金属超表面，通过加载接地金属枝节及在金属超表面贴片上蚀刻L型缝隙产生传输零点和额外的通带内谐振点，以此实现具有滤波响应的宽带天线。
具体而言，本实施例的接地金属枝节相当于并联式四分之一短路短截线的阻带效应，产生天线的下边带零点；金属超表面以及蚀刻在超表面贴片上的L型 缝隙可以在贴片上实现反向的电流分布，产生天线的上边带零点，实现滤波响应，边带具有较好的选择性，阻带抑制好。
为了进一步说明，增加了如图8(a)-8(c)所示的天线作为对比，如图8(a)的天线I，天线I仅包含缝隙耦合馈电的超表面结构1；图8(b)所示的天线II是在天线I的基础上，在超表面结构1下方增加接地金属枝节4及金属接地柱5；图8(c)的天线III在天线II的基础上，在超表面结构1上增加L型缝隙2。由图9(a)-9(b)可以发现，采用缝隙耦合馈电的超表面天线自身由于高次模式的反向电流分布在33.25GHz产生上边带零点；而加载接地金属枝节后，在低频23.25GHz产生下边带零点，形成下阻带；在超表面贴片上蚀刻L型缝隙后，改变了超表面电流的电流分布，在32.75GHz引入新的上边带零点，并且原33.25GHz处的零点移动到30.5GHz，上边带的边缘滚降性和上阻带抑制得到改善。由于该天线没有额外的滤波器/谐振器或滤波电路，可大大减少射频前端的体积，并且没有额外的插入损耗；另外，滤波结构的引入加入了电容式、电感式的谐振，也会影响天线的阻抗，从而引入了通带内的谐振点，拓宽了天线带宽，可以在紧凑高增益的结构下实现滤波性能。该天线结构简单，可在集成的结构下实现±45°双极化工作，并具有高选择性、高阻带抑制水平的滤波响应，适用于5G毫米波基站天线的功能融合设计。
实施例2
一种通信设备，包括如实施例1所述的基于超表面的双极化宽带毫米波滤波天线。
上述实施例为本发明较佳的实施方式，但本发明的实施方式并不受所述实施例的限制，其他的任何未背离本发明的精神实质与原理下所作的改变、修饰、替代、组合、简化，均应为等效的置换方式，都包含在本发明的保护范围之内。

Claims (10)

  1. 基于超表面的双极化宽带毫米波滤波天线，其特征在于，包括两层叠加设置的介质基板，下层介质基板的上表面及下表面分别设置上层金属地板及下层金属地板，所述上层介质基板的上表面设置超表面结构，所述超表面结构包括N个呈阵列排布的金属贴片，每个金属贴片上蚀刻缝隙，所述上层介质基板与上层金属地板相连，上层金属地板蚀刻耶路撒冷十字缝隙。
  2. 根据权利要求1所述的双极化宽带毫米波滤波天线，其特征在于，还包括接地金属枝节及金属接地柱，所述接地金属枝节设置在金属贴片的下方，且位于上层介质基板，所述金属接地柱一端与接地金属枝节连接，另一端与上层金属地板连接。
  3. 根据权利要求1所述的双极化宽带毫米波滤波天线，其特征在于，所述超表面结构与耶路撒冷十字缝隙呈45度夹角。
  4. 根据权利要求3所述的双极化宽带毫米波滤波天线，其特征在于，所述超表面结构包括四个金属贴片，每个金属贴片上蚀刻两条L型缝隙，两条L型缝隙关于金属贴片对角线对称，且分别与金属贴片的相邻边垂直。
  5. 根据权利要求4所述的双极化宽带毫米波滤波天线，其特征在于，L型缝隙的加载使超表面结构的高次模式向低频移动，改善通带边缘的滚降性，并且引入高频第二零点，提高高频带外抑制水平。
  6. 根据权利要求2所述的双极化宽带毫米波滤波天线，其特征在于，所述接地金属枝节和金属接地柱的排布方向均与耶路撒冷十字缝隙呈45度角。
  7. 根据权利要求1-6任一项所述的双极化宽带毫米波滤波天线，其特征在于，还包括两条共平面的金属带状馈线，位于耶路撒冷十字缝隙的正下方，两条金属带状馈线正交是通过一条短带状线的金属桥实现。
  8. 根据权利要求7所述的双极化宽带毫米波滤波天线，其特征在于，所述金属带状馈线和耶路撒冷十字缝隙周围采用隔离结构。
  9. 根据权利要求1所述的双极化宽带毫米波滤波天线，其特征在于，相邻金属贴片间距为0.01λg0～0.3λg0，其中，λg0为天线中心频率对应的介质有效波长。
  10. 一种通信设备，其特征在于，包括如权利要求1-9任一项所述的双极化宽带毫米波滤波天线。
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