WO2022027950A1 - 毫米波双圆极化透镜天线及电子设备 - Google Patents

毫米波双圆极化透镜天线及电子设备 Download PDF

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Publication number
WO2022027950A1
WO2022027950A1 PCT/CN2021/076024 CN2021076024W WO2022027950A1 WO 2022027950 A1 WO2022027950 A1 WO 2022027950A1 CN 2021076024 W CN2021076024 W CN 2021076024W WO 2022027950 A1 WO2022027950 A1 WO 2022027950A1
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circularly polarized
layer
lens
feed
metal patch
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PCT/CN2021/076024
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English (en)
French (fr)
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蒋之浩
洪伟
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东南大学
网络通信与安全紫金山实验室
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Priority to US17/775,896 priority Critical patent/US20220399653A1/en
Publication of WO2022027950A1 publication Critical patent/WO2022027950A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/061—Two dimensional planar arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/06—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using refracting or diffracting devices, e.g. lens
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/44—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element
    • H01Q3/46—Active lenses or reflecting arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0414—Substantially flat resonant element parallel to ground plane, e.g. patch antenna in a stacked or folded configuration
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/045—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means
    • H01Q9/0457—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means electromagnetically coupled to the feed line

Definitions

  • the invention belongs to the field of electronic devices of wireless communication systems, and in particular relates to a millimeter-wave double circularly polarized lens antenna and electronic equipment.
  • the lens antenna is a transmissive electromagnetic wave radiation device that can generate a far-field focused beam, which can be widely used in wireless communication and satellite communication systems.
  • the beamforming of the lens antenna does not depend on the wave path difference generated by the different propagation distances of electromagnetic waves, but is based on the transmissive phase shift provided by its subwavelength resonant or non-resonant unit, so it has the advantages of light weight, low cost Profile, conformal and other advantages.
  • the difference between it and the planar reflectarray antenna is that the feed source of the lens antenna and the beam generated by the lens are located on both sides of the lens, so the feed source will not block the beam formed by the lens, making it easier to achieve polarization A beam with higher purity and lower sidelobes.
  • the lens antenna needs to have high transmission efficiency in addition to the required phase shift per element, its design is more challenging than that of a reflectarray.
  • Most of the existing lens antennas use dynamic phase or rotational phase alone. Based on this, a variety of single-linearly polarized and single-circularly polarized lens antennas have been developed, as well as dual-linearly polarized lens antennas composed of isotropic elements.
  • the existing dual circularly polarized lens antennas with independent beamforming need to use two functional layers.
  • the bottom layer is a dual linear polarized lens, which can independently conduct horizontal polarization and vertical polarization.
  • Phase shift the upper layer is a circular polarizer, which converts horizontal/vertical linearly polarized waves into left-handed/right-handed circularly polarized waves. Due to the use of two functional layers, the thickness of the realized double circularly polarized lens is close to or even more than one wavelength, and the bandwidth is very narrow.
  • the 3dB axial ratio bandwidth and the 3dB gain bandwidth are both less than 8%.
  • the present invention discloses a millimeter-wave dual circularly polarized lens antenna and electronic equipment.
  • the lens antenna has dual circularly polarized independent beamforming, wide working bandwidth, small gain fluctuation, and high circularly polarized purity and low Profile and other characteristics, can efficiently realize broadband dual circularly polarized high-gain directional beams pointing in different directions.
  • a millimeter-wave double circularly polarized lens antenna is characterized in that: it comprises a broadband circularly polarized plane feed array and a double circularly polarized plane lens arranged in parallel, and the broadband circularly polarized plane feed array passes through the double circularly polarized plane lens output or receive signal where,
  • the double-circularly polarized plane lens includes a plurality of double-circularly polarized transmissive phase shift units arranged periodically, and each double-circularly polarized transmissive phase shift unit includes an upper-layer slotted stacked metal patch, and two circular polarized transmissive phase shift units. a second metal floor with a shaped slot, a lower layer with slotted stacked metal patches, two upper layer microstrip lines and two lower layer microstrip lines;
  • the upper slotted stacked metal patch faces the broadband circularly polarized planar feed array
  • the upper slotted stacked metal patch and the lower slotted stacked metal patch are both double-layered metal patch stacked structures
  • the upper slotted stacked metal patch The two microstrip lines of the lower layer and the upper layer of the chip are in the same metal layer and are physically connected; the upper layer and the two lower microstrip lines of the lower layer slotted stacked metal patch are in the same metal layer and are physically connected;
  • each upper-layer microstrip line and the lower-layer microstrip line are provided with metal through holes connected to each other and passing through the circular gap; the upper-layer slotted stacked metal patch and the lower slotted stacked metal patch pass through the two upper-layer microstrip lines, The two lower-layer microstrip lines are connected to the two metal vias.
  • each double circularly polarized transmissive phase shift unit is a transmissive half-wave plate, and the upper layer of the stacked metal patch with grooves, the second metal floor and the lower layer of the stacked metal patch with grooves are arranged between layers.
  • the upper-layer slotted stacked metal patch and the lower slotted stacked metal patch are respectively provided with four rectangular slots with outward openings in the ⁇ 45° direction.
  • the phase shift of any one of the two microstrip lines in the upper layer of the dual circularly polarized transmissive phase shift unit is the left-handed circularly polarized wave and the right-handed circularly polarized wave required by the unit
  • the phase shift of the other microstrip line is one quarter of the sum of the phase shifts of the left-hand circularly polarized wave and the right-hand circularly polarized wave required by the cell plus or Subtracting 90°
  • the in-plane rotation angle of the dual-circularly polarized transmissive phase-shift unit is equal to one-fourth of the difference between the phase shifts of the left- and right-handed circularly polarized waves required by the unit; for Achieve independently controllable dual circularly polarized millimeter beams.
  • the in-plane rotation angle of each dual-circularly polarized transmissive phase shift unit is 0°
  • the phase shifts of the upper two microstrip lines of the dual-circularly polarized transmissive phase shift unit are respectively two required by the unit.
  • Half of the phase shift of each linear polarization, and the pattern and size of the upper two microstrip lines and the lower two microstrip lines are exactly the same; it is used to realize an independently controllable dual linear polarization beam.
  • the broadband circularly polarized planar feed array includes a plurality of feed antenna units, and each feed antenna unit includes four slot-coupled circularly polarized antenna units and a microstrip parallel feed circuit arranged in sequence.
  • Each slot-coupled circularly polarized antenna unit includes an upper metal patch with chamfered corners, a lower metal patch with chamfered corners, and a first metal floor, where an I-shaped coupling slot is set on the first metal floor.
  • the angle of the chamfered angle of the upper circular metal patch with chamfered corners and the lower circular metal patch with chamfered corners is -45° or +45°; the four gap coupling circles
  • the polarized antenna units are arranged in a sequential rotation manner, and the rotation angles are 0°, 90°, 0°, and 90° in turn;
  • the microstrip parallel feeding circuit feeds four circularly polarized antenna units, the microstrip parallel feeding circuit includes one input port and four output ports, the characteristic impedance of the input port is 50 ohms, and the characteristic impedance of the four output ports is 50 ohms.
  • the output phase is 0°, 90°, 180°, 270° or 0°, -90°, -180°, -270°.
  • the double circularly polarized flat lens comprises a first layer of lens substrate, a second layer of lens substrate, a third layer of lens substrate, and a fourth layer of lens substrate;
  • the upper layer has two layers of metal patches stacked with grooves. The layers are respectively attached to the upper and lower surfaces of the first layer substrate of the lens, the two layers of the lower layer with grooved stacked metal patches are respectively attached to the upper and lower surfaces of the fourth layer substrate of the lens, and the second metal floor is located on the second layer substrate of the lens and the lens. between the third layer of substrates.
  • the broadband circularly polarized planar feed array includes a feed upper substrate, a feed middle substrate and a feed bottom substrate, and the upper metal patch with chamfered corners is attached to the lower surface of the feed upper substrate, The lower metal patch with chamfered corners is attached to the upper surface of the feed medium substrate, the microstrip and feed circuit is attached to the lower surface of the feed bottom substrate, and the first metal floor is located between the feed intermediate substrate and the feed bottom substrate ;
  • There is an air layer between the upper substrate of the feed and the middle substrate of the feed which is used to control the coupling strength between the circular metal patch with chamfered corners on the upper layer and the circular metal patch with chamfered corners on the lower layer , the thickness is less than 0.15 wavelength.
  • the center of the broadband circularly polarized plane feed array and the center of the double circularly polarized plane lens are on the same line, the distance between the two is F, the diameter of the double circularly polarized plane lens is D, and F/D The value ranges from 0.3 to 1.5.
  • An electronic device is characterized in that it comprises a casing, and the casing is provided with one of the above-mentioned millimeter-wave double circularly polarized lens antennas.
  • a broadband dual circularly polarized millimeter wave plane lens antenna proposed by the present invention has the following advantages:
  • Dual circularly polarized independent beam control can be realized: By using dynamic phase and rotational phase at the same time, a single functional layer can realize independent control of the transmission phase of left-handed circularly polarized wave and right-handed circularly polarized wave.
  • the phase is obtained by connecting two microstrip transmission lines with different lengths connecting the upper and lower stacked metal patches, while the rotational phase is obtained by performing different in-plane rotations on each dual circularly polarized transmissive phase shift unit.
  • Fig. 1 provides the three-dimensional schematic diagram of the broadband double circularly polarized millimeter-wave double circularly polarized lens antenna of the present invention
  • Figure 2 shows a three-dimensional schematic diagram of a broadband circularly polarized planar feed array
  • FIG. 3 is a three-dimensional schematic diagram of a dual circularly polarized transmissive phase shift unit
  • Figure 4 shows the transmission phase shift of the left-handed/right-handed circularly polarized wave at 21 GHz of the double-circularly polarized transmission phase shift unit of the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna as a function of the length of the microstrip line ( ly) and the change distribution of the unit rotation angle
  • (4a) represents the transmission phase shift of right-handed incidence and left-handed output ( ⁇ (tLR)), and (4b) represents the transmission phase shift of left-handed incidence and right-handed output ( ⁇ (tRL));
  • Figure 5 shows the transmission amplitude of the left-handed/right-handed circularly polarized wave at 21 GHz of the double-circularly polarized transmission phase shift unit of the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna as a function of the length of the microstrip line (ly ) and the change distribution diagram of the unit rotation angle;
  • (5a) represents the transmission amplitude (TLR) of right-handed incidence and left-handed outgoing
  • (5b) represents the transmission amplitude (TRL) of left-handed incidence and right-handed outgoing
  • Figure 6 shows the phase distributions of the left-to-right and right-to-left circularly polarized transmissions of the elements on the double-circularly polarized plane lens of the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna and the corresponding double-circular polarization
  • (6a) represents the phase shift distribution diagram of left-handed to right-handed circular polarization ( ⁇ (tRL)), (6b) represents the distribution diagram of right-handed to left-handed circular polarization ( ⁇ (tLR)), (6c) represents the double circle The distribution diagram of the microstrip line length (ly) of the polarization transmission phase shift unit, (6d) represents the distribution diagram of the rotation angle of the dual circular polarization transmission phase shift unit;
  • Figure 7 shows the simulated and measured left-circular polarization and right-circular polarization normalization at 21 GHz when the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna is excited by a left-handed broadband circularly polarized planar feed array direction map;
  • (7a) represents the xz plane
  • (7b) represents the yz plane
  • Figure 8 shows the simulated and measured port reflection coefficient, gain and axial ratio at 21 GHz when the broadband double circularly polarized millimeter-wave double circularly polarized lens antenna is excited by a left-handed broadband circularly polarized planar feed array with frequency curve;
  • (8a) represents the port reflection coefficient
  • (8b) represents the gain and axial ratio
  • Figure 9 shows the simulated and measured left-circular polarization and right-circular polarization at 21 GHz when the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna is excited by a right-handed broadband circularly polarized planar feed array normalized pattern;
  • Figure 10 shows the simulated and measured gain and axis ratio curve with frequency at 21 GHz when the broadband double circularly polarized millimeter-wave double circularly polarized lens antenna is excited by a right-handed broadband circularly polarized planar feed array;
  • FIG. 11 is a cross-sectional view of the structure of a broadband circularly polarized planar feed array
  • FIG. 12 is a cross-sectional view of the structure of a double circularly polarized plane lens
  • 1-broadband circularly polarized plane feed array 2-double circularly polarized plane lens, 3-double circularly polarized transmission phase shift unit;
  • 1a-slot-coupled circularly polarized antenna element 1b-microstrip parallel feeding circuit, 1c-circular metal patch with chamfered corners on the upper layer, 1d-circular metal patch with chamfered corners on the lower layer, 1e-first Metal floor, 1f-feed upper substrate, 1g-feed middle substrate, 1h-feed bottom substrate;
  • 3a-upper slotted stacked metal patch 3b-circular slot, 3c-second metal floor, 3d-lower slotted stacked metal patch, 3e-upper microstrip line, 3f-lower microstrip line, 3g-metal Through hole, 3h-lens first layer substrate, 3i-lens second layer substrate, 3j-lens third layer substrate, 3k-lens fourth layer substrate, 3l-rectangular groove.
  • the invention proposes a broadband double circularly polarized millimeter-wave double circularly polarized lens antenna.
  • the structure consists of a broadband circularly polarized planar antenna array and a double circularly polarized planar lens, wherein the broadband circularly polarized planar feed array consists of four slot-coupled circularly polarized antenna elements and a micro
  • the dual circularly polarized plane lens is composed of subwavelength dual circularly polarized transmissive phase shift units arranged periodically, each unit includes an upper layer slotted stacked metal patch, one with two circular Slotted metal floor, and the lower stacked metal patch with slot, the upper stacked metal patch with slot and the lower stacked metal patch with slot are composed of two microstrip lines on the upper layer and two microstrip lines on the lower layer through two metal through holes connected, the length and rotation angle of the microstrip line of each unit are different.
  • This dual circularly polarized millimeter-wave dual circularly polarized lens antenna can achieve independent beamforming for left-handed and right-handed circularly polarized waves in a wide frequency band, with a 1dB gain and an axial ratio of ⁇ 2dB bandwidth of about 12%, and the lens The profile is only 0.11 wavelength.
  • the present invention has the advantages of lower profile, wider axial ratio bandwidth, wider gain bandwidth, etc., and has broad application in the future fifth-generation mobile communication, satellite communication and other fields. application prospects.
  • a broadband dual circularly polarized millimeter-wave dual circularly polarized lens antenna of the present invention comprises a broadband circularly polarized plane feed array 1 and a double circularly polarized plane lens 2;
  • the broadband circularly polarized planar feed array 1 is located near the focal plane of the double circularly polarized planar lens 2;
  • the broadband circularly polarized planar feed array 1 consists of four slot-coupled circularly polarized antenna elements 1a and a
  • the microstrip parallel feeding circuit 1b is composed of, each slot-coupled circularly polarized antenna unit 1a consists of a circular metal patch 1c with a beveled corner on the upper layer, a circular metal patch 1d with a beveled corner on the lower layer, and an I-shaped
  • the metal floor of the coupling slot is composed of 1e;
  • the double circularly polarized plane lens 2 is composed of double circularly polarized transmissive phase shift units 3 arranged periodically, and each double circularly polarized transmissive phase
  • a microstrip line 3e and two lower microstrip lines 3f are connected 3g through two metal through holes; any one of the two microstrip lines 3e in the upper layer of each dual circularly polarized transmissive phase shift unit 3
  • the phase shift is a quarter of the sum of the phase shifts of the left-hand circularly polarized wave and the right-hand circularly polarized wave required by the unit, and the phase shift of the other microstrip line is the left-hand circularly polarized wave required by the unit.
  • each dual-circularly polarized transmissive phase shift unit 3 is equal to the left-handed circularity required for that unit Quarter of the difference between the phase shifts of polarized waves and right-hand circularly polarized waves.
  • the broadband circularly polarized planar feed array 1 includes a feed upper substrate 1f, a feed middle substrate 1g and a feed bottom substrate 1h, and the upper metal patch 1c with chamfered corners is attached to the feed
  • the lower surface of the upper substrate 1f, the lower metal patch 1d with chamfered corners is attached to the upper surface of the middle layer substrate 1g of the feed source
  • the microstrip parallel feeding circuit 1b is attached to the lower surface of the bottom substrate 1h of the feed source
  • the first metal floor 1e is located on the bottom surface of the feed source. Between the feed middle substrate 1g and the feed bottom substrate 1h.
  • the thickness is less than 0.15 wavelength.
  • the double circularly polarized flat lens 2 includes a lens first layer substrate 3h, a lens second layer substrate 3i, a lens third layer substrate 3j and a lens fourth layer substrate 3k.
  • the dual-circular polarization transmissive phase shift unit 3 includes: an upper-layer slotted stacked metal patch 3a and a lower slotted stacked metal patch 3d are both double-layer metal layer structures, and the metal floor 3c is a single-layer metal layer structure, wherein the stacking
  • the lower and upper two microstrip lines 3e of the chip 3a are in the same metal layer and are physically connected; the upper layer and 3f of the lower layer slotted stacked metal patch 3d are in the same metal layer and are physically connected.
  • the upper layer grooved stacked metal patch 3a is attached to the upper and lower surfaces of the first layer substrate 3h of the lens
  • the lower layer grooved stacked metal patch 3d is attached to the upper and lower surfaces of the fourth layer substrate 3k of the lens
  • the metal floor 3c is located on the second layer of the lens.
  • the metal through holes 3g are located on both sides of the circular gap 3b, and the two are concentric.
  • the broadband circularly polarized plane feed array can radiate left-handed/right-handed circularly polarized waves in a wide frequency band, and the center of the broadband circularly polarized plane feed array and the center of the double circularly polarized plane lens are at On the same line, the distance between the two is F, the diameter of the plane reflection array is D, and the value of F/D should be between 0.3 and 1.5, which is set to 0.85 here.
  • the broadband circularly polarized planar feed array is composed of four slot-coupled circularly polarized antenna elements and a microstrip parallel feed circuit arranged in sequence. It consists of a metal patch, a circular metal patch with chamfered corners on the lower layer, and a metal floor with an I-shaped coupling slot. Between the upper substrate of the feed source and the middle substrate of the feed source is an air layer to control the coupling strength between the upper circular metal patch with chamfered corners and the lower circular metal patch with chamfered corners.
  • the axial ratio of the radiated waves of the antenna element can be adjusted in a wide frequency range, thereby realizing broadband circularly polarized radiation; by controlling The position of the chamfered corners of the upper and lower circular patches is at -45° or +45°, which can realize left-handed or right-handed circularly polarized radiation.
  • By optimizing the size of the I-shaped coupling slot and its relative position to the patch better impedance matching can be achieved, resulting in a reflection coefficient of less than -15dB over a wide frequency range.
  • the radiation to be realized is left-handed or right-handed circularly polarized waves, and the output phases of the four output ports are sequentially 0°, 90°, 180°, 270° or 0°, -90°, -180°, -270°.
  • the realized four-element broadband circularly polarized planar feed array can have a circularly polarized beam with high symmetry, high polarization purity and stable gain, and its 2dB axial ratio bandwidth and 1dB gain bandwidth both exceed 25%.
  • the double-circularly polarized plane lens is composed of double-circularly polarized transmissive phase shift units arranged in a periodical manner, and the unit period is selected as 1/2 wavelength here.
  • Each unit is a transmission half-wave plate, so that the transmitted wave of the incident left-handed/right-handed circularly polarized wave becomes a right-handed/left-handed circularly polarized wave, and the left-handed circularly polarized wave and the right-handed circularly polarized wave can be independently controlled
  • the reflected phase ( ⁇ RL and ⁇ LR) of the polarized wave is adjusted, thereby realizing independent beamforming for left-handed/right-handed circularly polarized waves.
  • the dual circularly polarized transmissive phase shift unit consists of an upper slotted stacked metal patch, a metal floor dug with two circular slits, and a lower slotted stacked metal patch, the upper slotted stacked metal patch and the lower band
  • the slot stacked metal patch is connected by two microstrip lines on the upper layer and two microstrip lines on the lower layer through two metal through holes.
  • the dielectric layer generally uses a mixed high-frequency circuit board, FR4, etc., which plays the role of separating and supporting the metal layer.
  • the metal layer can be made of materials such as copper or gold.
  • the use of stacked patches can effectively increase the bandwidth, and in order to reduce the coupling between units, the upper-layer slotted metal patch and the lower slotted metal patch of the dual circularly polarized transmissive phase shift unit are in the ⁇ 45° direction.
  • the upper slotted stacked metal patch of each unit receives the circularly polarized wave from the broadband circularly polarized planar feed array, and transforms the two orthogonal linearly polarized components of the incident wave into two orthogonal linearly polarized components in the x and y directions, respectively.
  • the guided waves in the two connected upper-layer microstrip lines are then transmitted to the lower two microstrip lines on the fourth layer of metal through the metal through holes on the metal floor, and are stacked via the lower layer with slots
  • the metal patch radiates, thereby forming a transmitted wave. Due to the different lengths of the transmission lines, the transmission phases of the two orthogonal linear polarizations are different.
  • the total length difference of the two microstrip transmission lines connected to the patch in the x and y directions is one-half wavelength, so
  • the transmission phases of the two orthogonal linearly polarized components are 180 degrees out of phase, so that the transmitted wave changes from left-handed/right-handed circular polarization to right-handed/left-handed circular polarization.
  • the reflection phases of the left-handed and right-handed circularly polarized waves can be independently controlled, and both can achieve a 360-degree phase shift, so as to meet the requirements of the formation of almost any beam requirement.
  • any one of the two microstrip lines in the upper layer of the dual circularly polarized transmissive phase shift unit whose phase shift is the required left-hand circularly polarized wave and 1/4 of the sum of the phase shifts of the right-hand circularly polarized waves
  • the phase shift of the other microstrip line is the sum of the phase shifts of the left-handed circularly polarized waves and the right-handed circularly polarized waves required by the unit 1/4 plus or minus 90°
  • the in-plane rotation angle of the dual circularly polarized transmissive phase shift unit is equal to the required phase shift of the left-hand circularly polarized wave and the right-handed circularly polarized wave of the unit a quarter of the difference.
  • Figure 4 shows the left-handed/right-handed circularly polarized wave transmission phase shift of the double-circularly polarized transmission phase shift unit of the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna with the length of the microstrip line (ly) It can be seen that by changing the length of the microstrip line and the unit rotation angle at the same time, independent phase shifts of left-handed and right-handed circularly polarized waves can be achieved, and both can cover the 360° phase shift range.
  • FIG. 5 shows the transmission amplitude of the left-handed/right-handed circularly polarized wave of the double-circularly polarized transmission phase shift unit of the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna as a function of the microstrip line length (ly) and The variation distribution diagram of the unit rotation angle, it can be seen that while changing the length of the microstrip line and the unit rotation angle, the transmission amplitudes of the left-handed and right-handed circularly polarized waves are kept above -2dB, ensuring a relatively stable and relatively stable high transmittance.
  • Figure 6 shows the phase distributions of the left-to-right and right-to-left circularly polarized transmissions of the elements on the double-circularly polarized plane lens of the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna and the corresponding double-circular polarization
  • Figure 7 shows the simulated and measured left-handed circular polarization in the xz plane and the yz plane at 21 GHz when the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna is excited by a left-handed broadband circularly polarized planar feed array. From the normalized pattern of right-handed circular polarization, it can be seen that a right-handed circularly polarized high-gain beam is generated in the +20° direction in the yz plane, and the measurement results are in good agreement with the simulation results.
  • Figure 8 shows the simulated and measured port reflection coefficients, axial ratios and right-handed circular polarities at 21 GHz when the broadband dual-circularly polarized millimeter-wave dual-circularly polarized lens antenna is excited by a left-handed broadband circularly polarized planar feed array. It can be seen that the measured and simulated results are consistent. In the entire frequency band, the reflection coefficient is less than -14dB, the maximum gain is about 22.3dBic, and the 1dB gain bandwidth and 2dB ratio bandwidth are about 12.4%.
  • Figure 9 shows the simulated and measured left-handed circular poles in the xz plane and the yz plane at 21 GHz when the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna is excited by a right-handed broadband circularly polarized planar feed array Normalized and right-handed circularly polarized patterns, it can be seen that a left-handed circularly polarized high-gain beam is generated in the -20° direction in the xz plane, and the measurement results are in good agreement with the simulation results.
  • Figure 10 shows the simulated and measured port reflection coefficients, axial ratios and left-handed circles at 21 GHz when the broadband double-circularly polarized millimeter-wave double-circularly polarized lens antenna is excited by a right-handed circular broadband circularly polarized planar feed array.
  • the polarization gain varies with frequency. It can be seen that the measured and simulated results are stable. In the entire frequency band, the reflection coefficient is less than -14dB, the maximum gain is about 22.5dBic, and the 1dB gain bandwidth and 2dB ratio bandwidth are about 12.2%.

Abstract

本发明公开了一种毫米波双圆极化透镜天线及电子设备，天线包括宽带圆极化平面馈源阵列和双圆极化平面透镜，在平面馈源阵列中，同时利用双层堆叠贴片实现宽带圆极化，并利用顺序旋转馈电结构进一步拓展带宽并提高极化纯度，在平面透镜中，利用小型化堆叠贴片和微带真时延移相结构，在较宽频带内获得对左旋及右旋圆极化波透射相位的独立调控。本发明的透镜天线能够实现双圆极化高定向波束，且对左旋圆极化波和右旋圆极化波的波束指向进行独立控制，同时实现透射式的双圆极化波束成形，克服了馈源阻挡等负面影响，能够得到很好的极化纯度和波束形状，具有宽带、轻便、集成度高、低成本等特性，在无线通信和卫星通信方面有广阔的应用前景。

Description

毫米波双圆极化透镜天线及电子设备 技术领域
本发明属于无线通信系统电子器件领域，具体涉及一种毫米波双圆极化透镜天线及电子设备。
背景技术
透镜天线是一种可产生远场聚焦波束的透射式电磁波辐射装置，其在无线通信和卫星通信系统中可被广泛应用。与传统抛物反射面天线不同，透镜天线的波束成形不依赖电磁波传播距离不同所产生的波程差，而是基于其亚波长谐振或非谐振单元所提供的透射式相移，因此具备轻便、低剖面、可共形等优势。此外，其与平面反射阵天线的区别在于，透镜天线的馈源和透镜所产生的波束分别位于透镜的两侧，因此馈源不会对透镜所形成的波束产生阻挡，从而更容易实现极化纯度较高、副瓣较低的波束。但是，由于透镜天线除了每个单元需要产生所需的相移外，还需要具备高透射效率，因此，其设计比反射阵所面临的挑战更大。已有的透镜天线大多单独利用动态相位或旋转相位，基于此，多种单线极化和单圆极化的透镜天线被研制出，以及采用各向同性单元构成的双线极化透镜天线。
目前对于波束方向可独立控制的双圆极化透镜天线的研究很少，尽管其所提供的圆极化波频率复用在多个通信的领域有着重要的潜在应用。此前已有的可独立波束成形的双圆极化透镜天线需要采用两个层功能层，底层为一个双线极化透镜，可以对相互正交的水平极化波和垂直极化波进行独立地移相，上层为一个圆极化器，将水平/垂直线极化波转变为左旋/右旋圆极化波。由于采用了两个功能层，所实现的双圆极化透镜厚度均接近甚至超过一个波长，且带宽很窄，3dB轴比带宽和3dB增益带宽均小于8％。
发明内容
技术目的：针对的不足，本发明公开了一种毫米波双圆极化透镜天线及电子设备，透镜天线具有双圆极化独立波束成形、工作宽带、增益波动小、圆极化纯度高、低剖面等特性，可以高效地实现指向不同方向的宽带双圆极化高增益定向波束。
技术方案：为实现上述技术目的，本发明采用了如下技术方案：
一种毫米波双圆极化透镜天线，其特征在于：包括平行设置的宽带圆极化平面馈源阵列和双圆极化平面透镜，宽带圆极化平面馈源阵列通过双圆极化平面透镜输出或接收 信号，其中，
所述双圆极化平面透镜包括周期排布的多个双圆极化透射式相移单元，每个双圆极化透射式相移单元包括上层带槽堆叠金属贴片、设有两个圆形缝隙的第二金属地板、下层带槽堆叠金属贴片、两条上层微带线和两条下层微带线；
所述上层带槽堆叠金属贴片朝向宽带圆极化平面馈源阵列，上层带槽堆叠金属贴片和下层带槽堆叠金属贴片均为双层金属贴片堆叠结构，上层带槽堆叠金属贴片的下层和上层两条微带线在同一层金属层且在物理上相连接；下层带槽堆叠金属贴片的上层和两条下层微带线在同一层金属层且在物理上相连接；
各上层微带线和下层微带线的外端设置相互连接且穿过圆形缝隙的金属通孔；上层带槽堆叠金属贴片和下层带槽堆叠金属贴片通过两条上层微带线、两条下层微带线和两个金属通孔相连。
优选地，每个双圆极化透射式相移单元均为透射式半波片，上层带槽堆叠金属贴片、第二金属地板以及下层带槽堆叠金属贴片的层与层之间均设有一个介质层；
所述上层带槽堆叠金属贴片和下层带槽堆叠金属贴片在±45°方向上分别设有四个开口向外的矩形槽。
优选地，所述双圆极化透射式相移单元的上层两条微带线中的任意一条微带线，其相移为该单元所需的左旋圆极化波和右旋圆极化波的相移之和的四分之一，另一条微带线的相移为该单元所需的左旋圆极化波和右旋圆极化波的相移之和的四分之一加上或减去90°，双圆极化透射式相移单元的平面内旋转角度等于该单元所需的左旋圆极化波和右旋圆极化波的相移之差的四分之一；用于实现可独立控制的双圆极化毫米波束。
优选地，每个双圆极化透射式相移单元的平面内旋转角度为0°，双圆极化透射式相移单元的上层两条微带线的相移分别为该单元所需的两个线极化的相移的二分之一，且上层两条微带线和下层两条微带线图案和尺寸完全相同；用于实现可独立控制的双线极化波束。
优选地，所述宽带圆极化平面馈源阵列包括多个馈源天线单元，每个馈源天线单元包括四个按顺序旋转排布的缝隙耦合圆极化天线单元和一个微带并馈电路，每个缝隙耦合圆极化天线单元包括上层带斜切角金属贴片、下层带斜切角金属贴片和第一金属地板，第一金属地板上开设工字形耦合缝隙。
优选地，所述上层带斜切角的圆形金属贴片、下层带斜切角的圆形金属贴片的斜切 角的角度为-45°或+45°；所述四个缝隙耦合圆极化天线单元按照顺序旋转方式排布，旋转角度依次为0°、90°、0°、90°；
所述微带并馈电路对四个圆极化天线单元进行馈电，微带并馈电路包括一个输入端口和四个输出端口，输入端口的特征阻抗为50欧姆，四个输出端口的特征阻抗为70欧姆，输出相位依次为0°、90°、180°、270°或0°、-90°、-180°、-270°。
优选地，所述双圆极化平面透镜包括透镜第一层基片、透镜第二层基片、透镜第三层基片、和透镜第四层基片；上层带槽堆叠金属贴片的两层分别附着在透镜第一层基片的上下表面，下层带槽堆叠金属贴片的两层分别附着在透镜第四层基片的上下表面，第二金属地板位于透镜第二层基片和透镜第三层基片之间。
优选地，所述宽带圆极化平面馈源阵列包括馈源上层基片、馈源中层基片和馈源底层基片，上层带斜切角金属贴片附着在馈源上层基片下表面，下层带斜切角金属贴片附着在馈源中层基片上表面，微带并馈电路附着在馈源底层基片下表面，第一金属地板位于馈源中层基片和馈源底层基片之间；馈源上层基片和馈源中层基片之间是一个空气层，用于控制上层带斜切角的圆形金属贴片和下层带斜切角的圆形金属贴片之间的耦合强度，厚度小于0.15波长。
优选地，所述宽带圆极化平面馈源阵列的中心和双圆极化平面透镜的中心在同一条线上，两者距离为F，双圆极化平面透镜的直径为D，F/D的取值范围为0.3～1.5。
一种电子设备，其特征在于：包括壳体，所述壳体内设有一个以上所述的毫米波双圆极化透镜天线。
有益效果：由于采用了上述技术方案，本发明提出的一种宽带双圆极化毫米波平面透镜天线，具有如下优势：
(1)可以实现双圆极化独立波束控制：通过同时采用动态相位和旋转相位，可以实现单个功能层对左旋圆极化波和右旋圆极化波的透射相位独立的调控，其中，动态相位通过连接上层堆叠金属贴片和下层堆叠金属贴片的两条具有不同长度的微带传输线获得，而旋转相位通过对每个双圆极化透射式相移单元进行不同的平面内旋转获得。
(2)具有透射式构架：与反射阵不同，由于该发明实现了透射式的双圆极化波束成形，克服了馈源阻挡等负面影响，因此极化纯度和波束形状可以得到很好的控制。
(3)具有宽带特性：这是由于采用了宽带圆极化平面馈源阵列和宽带双圆极化平 面透镜，在平面馈源阵列中，同时利用双层堆叠贴片实现宽带圆极化，并利用顺序旋转馈电结构进一步拓展带宽并提高极化纯度，在平面透镜中，利用小型化堆叠贴片和微带真时延移相结构，在较宽频带内获得对左旋/右旋圆极化波透射相位的独立调控。因此，可以在超过12％的带宽内实现纯度很高且指向不同方向的左旋和右旋圆极化波束。
(4)具有轻便、集成度高、低成本等特性：这是因为平面透镜只有一个功能层，且采用了具有亚波长厚度的介质基片，总厚度可小于0.11波长，比此前已有的采用两个功能层的双圆极化透镜的厚度减小到约1/10。
附图说明
图1给出了本发明的宽带双圆极化毫米波双圆极化透镜天线的三维示意图；
图2给出了宽带圆极化平面馈源阵列的三维示意图；
图3是双圆极化透射式相移单元的三维示意图；
图4给出了所述宽带双圆极化毫米波双圆极化透镜天线的双圆极化透射式相移单元在21GHz的左旋/右旋圆极化波透射相移随微带线长度(ly)和单元旋转角度的变化分布图
(4a)表示右旋入射、左旋出射的透射相移(φ(tLR))，(4b)表示左旋入射、右旋出射的透射相移(φ(tRL))；
图5给出了所述宽带双圆极化毫米波双圆极化透镜天线的双圆极化透射式相移单元在21GHz的左旋/右旋圆极化波透射幅度随微带线长度(ly)和单元旋转角度的变化分布图；
(5a)表示右旋入射、左旋出射的透射幅度(TLR)、(5b)表示左旋入射、右旋出射的透射幅度(TRL)；
图6给出了所述宽带双圆极化毫米波双圆极化透镜天线的双圆极化平面透镜上的单元左旋到右旋和右旋到左旋圆极化透射相位分布以及对应的双圆极化透射式相移单元微带线长度(ly)和双圆极化透射式相移单元旋转角度的分布图；
(6a)表示左旋到右旋圆极化相移分布图(φ(tRL))、(6b)表示右旋到左旋圆极化相移分布图(φ(tLR))、(6c)表示双圆极化透射式相移单元微带线长度(ly)分布图、(6d)表示双圆极化透射式相移单元旋转角度的分布图；
图7给出了所述宽带双圆极化毫米波双圆极化透镜天线用左旋宽带圆极化平面馈源 阵列激励时在21GHz的仿真和实测左旋圆极化和右旋圆极化归一化方向图；
(7a)表示xz平面、(7b)表示yz平面；
图8给出了所述宽带双圆极化毫米波双圆极化透镜天线用左旋宽带圆极化平面馈源阵列激励时在21GHz的仿真和实测的端口反射系数、增益和轴比随频率变化曲线；
(8a)表示端口反射系数、(8b)表示增益和轴比；
图9给出了所述宽带双圆极化毫米波双圆极化透镜天线用右旋宽带圆极化平面馈源阵列激励时在21GHz的仿真和实测的左旋圆极化和右旋圆极化归一化方向图；
(9a)表示xz平面、(b)表示yz平面；
图10给出了所述宽带双圆极化毫米波双圆极化透镜天线用右旋宽带圆极化平面馈源阵列激励时在21GHz的仿真和实测的增益和轴比随频率变化曲线；
(10a)端口反射系数、(10b)增益和轴比；
图11为宽带圆极化平面馈源阵列的结构剖视图；
图12为双圆极化平面透镜的结构剖视图；
其中，1-宽带圆极化平面馈源阵列，2-双圆极化平面透镜，3-双圆极化透射式相移单元；
1a-缝隙耦合圆极化天线单元，1b-微带并馈电路，1c-上层带斜切角的圆形金属贴片，1d-下层带斜切角的圆形金属贴片，1e-第一金属地板，1f-馈源上层基片，1g-馈源中层基片，1h-馈源底层基片；
3a-上层带槽堆叠金属贴片，3b-圆形缝隙,3c-第二金属地板，3d-下层带槽堆叠金属贴片，3e-上层微带线，3f-下层微带线，3g-金属通孔，3h-透镜第一层基片，3i-透镜第二层基片，3j-透镜第三层基片，3k-透镜第四层基片，3l-矩形槽。
具体实施方式
本发明提出了一种宽带双圆极化毫米波双圆极化透镜天线。该结构由一个宽带圆极化平面天线阵列和一个双圆极化平面透镜组成，其中，宽带圆极化平面馈源阵列由四个按顺序旋转排布的缝隙耦合圆极化天线单元和一个微带并馈电路构成，而双圆极化平面透镜由亚波长双圆极化透射式相移单元成周期排布组成，每个单元包含一个上层带槽堆叠金属贴片、一个挖有两个圆形缝隙的金属地板、以及下层带槽堆叠金属贴片，上层带槽堆叠金属贴片和下层带槽堆叠金属贴片由上层两条微带线和下层两条微带线通过两 个金属通孔相连，每个单元的微带线的长度和旋转角度不同。此双圆极化毫米波双圆极化透镜天线可在一个宽频段内实现对左旋和右旋圆极化波的独立波束成形，其1dB增益和轴比<2dB带宽约为12％，且透镜剖面仅为0.11波长。相比于已有的双圆极化透镜天线，本发明具有更低的剖面、更宽的轴比带宽、更宽的增益带宽等优点，在未来第五代移动通信、卫星通信等领域具有广阔的应用前景。
下面结合附图对本发明做进一步说明。
如图1至图3所示，本发明的一种宽带双圆极化毫米波双圆极化透镜天线，天线包括一个宽带圆极化平面馈源阵列1和一个双圆极化平面透镜2；宽带圆极化平面馈源阵列1位于双圆极化平面透镜2的焦平面附近；宽带圆极化平面馈源阵列1由四个按顺序旋转排布的缝隙耦合圆极化天线单元1a和一个微带并馈电路1b组成，每个缝隙耦合圆极化天线单元1a由上层带斜切角的圆形金属贴片1c、下层带斜切角的圆形金属贴片1d和一个挖有工字形耦合缝隙的金属地板组成1e；该双圆极化平面透镜2由双圆极化透射式相移单元3成周期排布组成，每个双圆极化透射式相移单元3包含一个上层带槽堆叠金属贴片3a、一个挖有两个圆形缝隙3b的金属地板3c、以及下层带槽堆叠金属贴片3d，上层带槽堆叠金属贴片3a和下层带槽堆叠金属贴片3d由上层两条微带线3e和下层两条微带线3f通过两个金属通孔相连3g；每个双圆极化透射式相移单元3的上层两条微带线3e的其中任意一条微带线的相移为该单元所需的左旋圆极化波和右旋圆极化波的相移之和的四分之一，另一条微带线的相移为该单元所需的左旋圆极化波和右旋圆极化波的相移之和的四分之一加上或减去90°；每个双圆极化透射式相移单元3的平面内旋转角度等于该单元所需的左旋圆极化波和右旋圆极化波的相移之差的四分之一。
如图11所示，宽带圆极化平面馈源阵列1包括馈源上层基片1f、馈源中层基片1g和馈源底层基片1h，上层带斜切角金属贴片1c附着在馈源上层基片1f下表面，下层带斜切角金属贴片1d附着在馈源中层基片1g上表面，微带并馈电路1b附着在馈源底层基片1h下表面，第一金属地板1e位于馈源中层基片1g和馈源底层基片1h之间。馈源上层基片1f和馈源中层基片1g之间是一个空气层，用于控制上层带斜切角的圆形金属贴片1c和下层带斜切角的圆形金属贴片1d之间的耦合强度，厚度小于0.15波长。
如图12所示，双圆极化平面透镜2包括透镜第一层基片3h、透镜第二层基片3i、透镜第三层基片3j和透镜第四层基片3k。双圆极化透射式相移单元3包括：上层带槽 堆叠金属贴片3a和下层带槽堆叠金属贴片3d均为双层金属层结构，金属地板3c为单层金属层结构，其中堆叠贴片3a的下层和上层两条微带线3e在同一层金属层，是物理上相连接的；下层带槽堆叠金属贴片3d的上层和3f在同一层金属层，是物理上相连接的。上层带槽堆叠金属贴片3a附着在透镜第一层基片3h的上下表面，下层带槽堆叠金属贴片3d附着在透镜第四层基片3k的上下表面，金属地板3c位于透镜第二层基片3i和透镜第三层基片3j之间，金属通孔3g位于圆形缝隙3b两侧，两者同心。
本发明中，宽带圆极化平面馈源阵列可在一个很宽的频带内辐射左旋/右旋圆极化波，宽带圆极化平面馈源阵列的中心和双圆极化平面透镜的中心在同一条线上，两者距离为F，平面反射阵的直径为D，F/D的值应在0.3和1.5之间，此处设为0.85。
宽带圆极化平面馈源阵列由四个按顺序旋转排布的缝隙耦合圆极化天线单元和一个微带并馈电路组成，每个缝隙耦合圆极化天线单元由上层带斜切角的圆形金属贴片、下层带斜切角的圆形金属贴片和一个挖有工字形耦合缝隙的金属地板组成。馈源上层基片和馈源中层基片之间是一个空气层，用以控制上层带斜切角的圆形金属贴片和下层带斜切角的圆形金属贴片之间的耦合强度。通过控制上层和下层圆形贴片的斜切角部分的大小、以及空气层的厚度，可以在一个宽频段范围内调节该天线单元辐射波的轴比，从而实现宽带圆极化辐射；通过控制上层和下层圆形贴片的斜切角部分的位置在-45°或+45°，可以实现左旋或者右旋圆极化辐射。通过优化工字形耦合缝隙的尺寸和其与贴片的相对位置，可以获得较好的阻抗匹配，从而在一个宽频段范围内实现小于-15dB的反射系数。然而，由于单个单元增益较低、波束宽度太宽(约为90°)，用其激励透镜会产生较大的边缘溢出损耗。因此，为了形成较窄的波束并进一步扩展带宽，利用四个缝隙耦合圆极化天线单元，将其按照顺序旋转方式排布，它们的旋转角度依次为0°、90°、0°、90°，并利用一个微带并馈电路对四个圆极化天线单元进行馈电。该微带并馈电路输入端口的特征阻抗为50欧姆，四个输出端口的特征阻抗为70欧姆，根据所需实现的辐射为左旋或者右旋圆极化波，四个输出端口的输出相位依次为0°、90°、180°、270°或0°、-90°、-180°、-270°。所实现的四单元宽带圆极化平面馈源阵列可以具有对称度高、极化纯度高、增益稳定的圆极化波束，其2dB轴比带宽和1dB增益带宽均超过25％。
如图3所示，双圆极化平面透镜由双圆极化透射式相移单元成周期排布组成，单元 周期此处选择为1/2波长。每个单元均为透射式半波片，使得入射左旋/右旋圆极化波的透射波变为右旋/左旋圆极化波，且可以独立的控制左旋圆极化波和右旋圆极化波的反射相位(φRL和φLR)，从而实现对左旋/右旋圆极化波独立的波束成形。双圆极化透射式相移单元包含一个上层带槽堆叠金属贴片、一个挖有两个圆形缝隙的金属地板、以及下层带槽堆叠金属贴片，上层带槽堆叠金属贴片和下层带槽堆叠金属贴片由上层两条微带线和下层两条微带线通过两个金属通孔相连，这五层金属层两两之间均有一个介质层，因此一共有四层介质基片。介质层一般使用混压高频电路板、FR4等，起到分离和支撑金属层的作用，金属层可采用铜或金等材料。堆叠贴片的使用可以有效增加带宽，而为了减小单元之间的耦合，双圆极化透射式相移单元的上层带槽堆叠金属贴片和下层带槽堆叠金属贴片在±45°方向上含有四个矩形槽。每个单元的上层带槽堆叠金属贴片接收到宽带圆极化平面馈源阵列的圆极化波，将入射波的两个正交线极化分量分别转变为在x和y方向与贴片相连的上层两条微带线中的导行波，这两股导行波再通过金属地板上的金属通孔传输到第四层金属上的下层两条微带线，并经由下层带槽堆叠金属贴片辐射，从而形成透射波。由于传输线的长度不同，两个正交线极化的透射相位不一样，此处，在x和y方向与贴片相连的两个微带传输线的总长度差为二分之一个波长，从而两个正交线极化分量的透射相位相差180度，使得透射波从左旋/右旋圆极化变为右旋/左旋圆极化。通过控制不同单元的微带传输线的长度，以及单元中所有结构的旋转角度，可以对左旋和右旋圆极化波的反射相位进行独立控制，并均可以实现360度的相移，从而满足形成几乎任何波束的要求。具体地，需满足3个条件：1)双圆极化透射式相移单元的上层两条微带线中的任意一条微带线，其相移为该单元所需的左旋圆极化波和右旋圆极化波的相移之和的四分之一，2)另一条微带线的相移为该单元所需的左旋圆极化波和右旋圆极化波的相移之和的四分之一加上或减去90°，3)双圆极化透射式相移单元的平面内旋转角度等于该单元所需的左旋圆极化波和右旋圆极化波的相移之差的四分之一。
图4给出了所述宽带双圆极化毫米波双圆极化透镜天线的双圆极化透射式相移单元的左旋/右旋圆极化波透射相移随微带线长度(ly)和单元旋转角度的变化分布图，可以看出，同时改变微带线的长度和单元旋转角度，可以实现左旋和右旋圆极化波的独立相移，并且均能覆盖360°移相范围。图5给出了所述宽带双圆极化毫米波双圆极化透 镜天线的双圆极化透射式相移单元的左旋/右旋圆极化波透射幅度随微带线长度(ly)和单元旋转角度的变化分布图，可以看出，在改变微带线的长度和单元旋转角度的同时，左旋和右旋圆极化波的透射幅度均保持在-2dB以上，保证了较平稳且较高的透射率。
图6给出了所述宽带双圆极化毫米波双圆极化透镜天线的双圆极化平面透镜上的单元左旋到右旋和右旋到左旋圆极化透射相位分布以及对应的双圆极化透射式相移单元微带线长度(ly)和双圆极化透射式相移单元旋转角度的分布图，此分布对应地可以实现左旋波束指向(θL,φL)＝(20°,90°)而右旋波束指向(θR,φR)＝(20°,180°)。
图7给出了所述宽带双圆极化毫米波双圆极化透镜天线用左旋宽带圆极化平面馈源阵列激励时在21GHz的仿真和实测的在xz平面和yz平面内左旋圆极化和右旋圆极化归一化方向图，可以看到一个右旋圆极化高增益波束在yz平面内的+20°方向产生，且测量结果和仿真结果非常吻合。
图8给出了所述宽带双圆极化毫米波双圆极化透镜天线用左旋宽带圆极化平面馈源阵列激励时在21GHz的仿真和实测的端口反射系数、轴比和右旋圆极化增益随频率变化曲线，可以看到，实测和仿真结果稳合，在整个频段内，反射系数小于-14dB，最大增益约22.3dBic，1dB增益带宽和2dB轴比带宽大约为12.4％。
图9给出了所述宽带双圆极化毫米波双圆极化透镜天线用右旋宽带圆极化平面馈源阵列激励时在21GHz的仿真和实测的在xz平面和yz平面内左旋圆极化和右旋圆极化归一化方向图，可以看到一个左旋圆极化高增益波束在xz平面内的-20°方向产生，且测量结果和仿真结果非常吻合。
图10给出了所述宽带双圆极化毫米波双圆极化透镜天线用右旋圆宽带圆极化平面馈源阵列激励时在21GHz的仿真和实测的端口反射系数、轴比和左旋圆极化增益随频率变化曲线，可以看到，实测和仿真结果稳合，在整个频段内，反射系数小于-14dB，最大增益约22.5dBic，1dB增益带宽和2dB轴比带宽大约为12.2％。
以上所述仅是本发明的优选实施方式，应当指出：对于本技术领域的普通技术人员来说，在不脱离本发明原理的前提下，还可以做出若干改进和润饰，这些改进和润饰也应视为本发明的保护范围。

Claims (10)

  1. 一种毫米波双圆极化透镜天线，其特征在于：包括平行设置的宽带圆极化平面馈源阵列(1)和双圆极化平面透镜(2)，宽带圆极化平面馈源阵列(1)通过双圆极化平面透镜(2)输出或接收信号，其中，
    所述双圆极化平面透镜(2)包括周期排布的多个双圆极化透射式相移单元(3)，每个双圆极化透射式相移单元(3)包括上层带槽堆叠金属贴片(3a)、设有两个圆形缝隙(3b)的第二金属地板(3c)、下层带槽堆叠金属贴片(3d)、两条上层微带线(3e)和两条下层微带线(3f)；
    所述上层带槽堆叠金属贴片(3a)朝向宽带圆极化平面馈源阵列(1)，上层带槽堆叠金属贴片(3a)和下层带槽堆叠金属贴片(3d)均为双层金属贴片堆叠结构，上层带槽堆叠金属贴片(3a)的下层和上层两条微带线(3e)在同一层金属层且在物理上相连接；下层带槽堆叠金属贴片(3d)的上层和两条下层微带线(3f)在同一层金属层且在物理上相连接；
    各上层微带线(3e)和下层微带线(3f)的外端设置相互连接且穿过圆形缝隙(3b)的金属通孔(3g)；上层带槽堆叠金属贴片(3a)和下层带槽堆叠金属贴片(3d)通过两条上层微带线(3e)、两条下层微带线(3f)和两个金属通孔(3g)相连。
  2. 根据权利要求1所述的一种毫米波双圆极化透镜天线，其特征在于：每个双圆极化透射式相移单元(3)均为透射式半波片，上层带槽堆叠金属贴片(3a)、第二金属地板(3c)以及下层带槽堆叠金属贴片(3d)的层与层之间均设有一个介质层；
    所述上层带槽堆叠金属贴片(3a)和下层带槽堆叠金属贴片(3d)在±45°方向上分别设有四个开口向外的矩形槽。
  3. 根据权利要求1所述的一种毫米波双圆极化透镜天线，其特征在于：所述双圆极化透射式相移单元(3)的上层两条微带线(3e)中的任意一条微带线，其相移为该单元所需的左旋圆极化波和右旋圆极化波的相移之和的四分之一，另一条微带线的相移为该单元所需的左旋圆极化波和右旋圆极化波的相移之和的四分之一加上或减去90°，双圆极化透射式相移单元的平面内旋转角度等于该单元所需的左旋圆极化波和右旋圆极化波的相移之差的四分之一；用于实现可独立控制的双圆极化毫米波束。
  4. 根据权利要求1所述的一种毫米波双圆极化透镜天线，其特征在于：每个双圆极化透射式相移单元(3)的平面内旋转角度为0°，双圆极化透射式相移单元(3)的上层两条微带线(3e)的相移分别为该单元所需的两个线极化的相移的二分之一，且上层 两条微带线(3e)和下层两条微带线(3f)图案和尺寸完全相同；用于实现可独立控制的双线极化波束。
  5. 根据权利要求1所述的一种毫米波双圆极化透镜天线，其特征在于：所述宽带圆极化平面馈源阵列(1)包括多个馈源天线单元，每个馈源天线单元包括四个按顺序旋转排布的缝隙耦合圆极化天线单元(1a)和一个微带并馈电路(1b)，每个缝隙耦合圆极化天线单元(1a)包括上层带斜切角金属贴片(1c)、下层带斜切角金属贴片(1d)和第一金属地板(1e)，第一金属地板(1e)上开设工字形耦合缝隙。
  6. 根据权利要求5所述的一种毫米波双圆极化透镜天线，其特征在于：所述上层带斜切角的圆形金属贴片(1c)、下层带斜切角的圆形金属贴片(1d)的斜切角的角度为-45°或+45°；所述四个缝隙耦合圆极化天线单元(1a)按照顺序旋转方式排布，旋转角度依次为0°、90°、0°、90°；
    所述微带并馈电路(1b)对四个圆极化天线单元(1a)进行馈电，微带并馈电路(1b)包括一个输入端口和四个输出端口，输入端口的特征阻抗为50欧姆，四个输出端口的特征阻抗为70欧姆，输出相位依次为0°、90°、180°、270°或0°、-90°、-180°、-270°。
  7. 根据权利要求1所述的毫米波平面透镜天线，其特征在于：所述双圆极化平面透镜(2)包括透镜第一层基片(3h)、透镜第二层基片(3i)、透镜第三层基片(3j)、和透镜第四层基片(3k)；上层带槽堆叠金属贴片(3a)的两层分别附着在透镜第一层基片(3h)的上下表面，下层带槽堆叠金属贴片(3d)的两层分别附着在透镜第四层基片(3k)的上下表面，第二金属地板(3c)位于透镜第二层基片(3i)和透镜第三层基片(3j)之间。
  8. 根据权利要求5所述的毫米波平面透镜天线，其特征在于：所述宽带圆极化平面馈源阵列(1)包括馈源上层基片(1f)、馈源中层基片(1g)和馈源底层基片(1h)，上层带斜切角金属贴片(1c)附着在馈源上层基片(1f)下表面，下层带斜切角金属贴片(1d)附着在馈源中层基片(1g)上表面，微带并馈电路(1b)附着在馈源底层基片(1h)下表面，第一金属地板(1e)位于馈源中层基片(1g)和馈源底层基片(1h)之间；馈源上层基片(1f)和馈源中层基片(1g)之间是一个空气层，用于控制上层带斜切角的圆形金属贴片(1c)和下层带斜切角的圆形金属贴片(1d)之间的耦合强度，厚度小于0.15波长。
  9. 根据权利要求1所述的一种毫米波双圆极化透镜天线，其特征在于：所述宽带 圆极化平面馈源阵列(1)的中心和双圆极化平面透镜(2)的中心在同一条线上，两者距离为F，双圆极化平面透镜(2)的直径为D，F/D的取值范围为0.3～1.5。
  10. 一种电子设备，其特征在于：包括壳体，所述壳体内设有一个以上的如权利要求1-9任一所述的毫米波双圆极化透镜天线。
PCT/CN2021/076024 2021-01-28 2021-02-08 毫米波双圆极化透镜天线及电子设备 WO2022027950A1 (zh)

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