WO2021184921A1 - 升降压驱动电路、方法、空调器和计算机可读存储介质 - Google Patents

升降压驱动电路、方法、空调器和计算机可读存储介质 Download PDF

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Publication number
WO2021184921A1
WO2021184921A1 PCT/CN2020/142006 CN2020142006W WO2021184921A1 WO 2021184921 A1 WO2021184921 A1 WO 2021184921A1 CN 2020142006 W CN2020142006 W CN 2020142006W WO 2021184921 A1 WO2021184921 A1 WO 2021184921A1
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WIPO (PCT)
Prior art keywords
voltage
circuit
power tube
power
tube
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PCT/CN2020/142006
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English (en)
French (fr)
Inventor
黄招彬
赵鸣
曾贤杰
文先仕
徐锦清
张杰楠
龙谭
胡斌
关平达
井上薰
Original Assignee
美的集团股份有限公司
广东美的制冷设备有限公司
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Priority claimed from CN202010188159.6A external-priority patent/CN111313728A/zh
Priority claimed from CN202020341297.9U external-priority patent/CN211209607U/zh
Priority claimed from CN202010188837.9A external-priority patent/CN111224564B/zh
Priority claimed from CN202010188759.2A external-priority patent/CN111342685B/zh
Application filed by 美的集团股份有限公司, 广东美的制冷设备有限公司 filed Critical 美的集团股份有限公司
Publication of WO2021184921A1 publication Critical patent/WO2021184921A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

Definitions

  • This application relates to the technical field of motors, and in particular to a buck-boost drive circuit, a buck-boost drive method, an air conditioner, and a computer-readable storage medium.
  • the drive motor of the high-efficiency inverter compressor of the inverter air conditioner is usually a permanent magnet motor. Therefore, the iron loss of the motor is mainly affected by the DC bus voltage of the inverter controller.
  • the DC voltage can be appropriately adjusted to reduce the iron loss of the motor and improve the efficiency of the motor.
  • the power factor correction (PFC) of the inverter air conditioner does not have a voltage reduction function.
  • passive PFC, single-pulse and multi-pulse PFC do not have the function of adjusting the DC bus voltage, while a typical boost PFC can only perform step-up adjustment, but not step-down adjustment.
  • This application aims to solve at least one of the technical problems existing in the prior art or related technologies.
  • the first aspect of the present application provides a buck-boost driving circuit.
  • the second aspect of the present application provides another buck-boost driving circuit.
  • the third aspect of the present application provides yet another buck-boost driving circuit.
  • the fourth aspect of the present application provides a buck-boost driving method.
  • the fifth aspect of the present application provides another buck-boost driving method.
  • the sixth aspect of the present application provides yet another buck-boost driving method.
  • a seventh aspect of the present application provides an air conditioner.
  • the eighth aspect of the present application provides a computer-readable storage medium.
  • the first aspect of the present application provides a buck-boost drive circuit, including: a boost-type circuit configured to perform power factor correction processing or rectification processing on a power supply signal; and A step-down circuit, the input end of the step-down circuit is connected to the output end of the step-up circuit, and the step-down circuit includes: a first power tube and a second power tube, which are connected in series to the step-up circuit in sequence Between the high-voltage output terminal and the low-voltage output terminal of the type circuit, the two ends of the second power tube are led out as a high-voltage bus and a low-voltage bus. The bus voltage between the high-voltage bus and the low-voltage bus is stepped down and modulated.
  • the buck-boost adjustment of the bus voltage is realized, which can make the bus voltage higher than the peak value of the AC voltage or lower the bus voltage.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • the step-up circuit and the step-down circuit are provided with a plurality of semiconductor switches, the semiconductor switches are controlled by a controller, and the controller according to the above collected AC voltage, AC current, DC bus voltage and DC bus current At least one signal modulates the working state of the semiconductor switch, thereby adjusting the working state of the step-up circuit and/or the step-down circuit.
  • the boost circuit can be a totem pole circuit, or a combination of a rectifier and a PFC circuit.
  • the second aspect of the present application provides another buck-boost driving circuit, including: a totem pole circuit configured to perform power factor correction processing or rectification processing on a power supply signal; a step-down circuit, so The input end of the step-down circuit is connected to the output end of the totem pole circuit.
  • the step-down circuit includes: a first power tube and a second power tube, which are connected in series to the high-voltage output end of the totem pole circuit and Between the low-voltage output ends, the two ends of the second power tube lead to a high-voltage bus and a low-voltage bus, wherein the first power tube and the second power tube are controlled to be turned on alternately, and the high-voltage bus and the low-voltage bus
  • the voltage of the busbar decreases as the operating time of the load increases, and the step-down circuit is configured to perform step-down processing or filtering processing on the power supply signal.
  • the buck-boost adjustment of the bus voltage is realized, which can make the bus voltage higher than the peak value of the AC voltage or lower the bus voltage
  • the peak value of AC voltage is used to improve the efficiency and reliability of the motor.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • a plurality of semiconductor switches are provided in the totem pole circuit and the step-down circuit.
  • the semiconductor switches are controlled by a controller.
  • a signal modulates the working state of the semiconductor switch, and then adjusts the working state of the totem pole circuit and/or the step-down circuit.
  • the third aspect of the present application provides yet another buck-boost drive circuit, including: a step-down circuit, the step-down circuit includes: a bridge circuit, and any bridge arm of the bridge circuit is provided with one Semiconductor tube, the step-down circuit is configured to access the power supply signal input from the power supply terminal; the step-up circuit, the input end of the step-up circuit is connected to the output end of the step-down circuit, so
  • the boost circuit is configured to be able to boost the power supply signal;
  • a seventh power tube is connected to the two output terminals of the bridge circuit and is connected to the two input terminals of the boost circuit, so The seventh power tube is configured to be capable of freewheeling the boost circuit.
  • a step-down circuit and a step-up circuit are set in the drive circuit to realize the step-down adjustment of the bus voltage, which can make the bus voltage higher than the peak value of the AC voltage or lower the bus voltage.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • multiple semiconductor switches are provided in the step-down circuit and the step-up circuit.
  • the semiconductor switches are controlled by a controller. At least one signal modulates the working state of the semiconductor switch, thereby adjusting the working state of the step-down circuit and/or the step-up circuit.
  • the fourth aspect of the present application provides a buck-boost driving method, including: determining the AC voltage input to the driving circuit and the bus voltage of the driving circuit; controlling the AC voltage and the bus voltage according to the AC voltage and the bus voltage.
  • the step-down circuit operates in a filter mode or a step-down mode, and the step-up circuit is controlled to operate in a power factor correction mode or a rectification mode.
  • a step-up circuit and a step-down circuit are provided in the drive circuit, and according to the AC voltage and the bus voltage, the step-up circuit is controlled to operate in the power factor correction mode or the rectification mode, And controlling the step-down circuit to work in the filtering mode or the step-down mode to achieve the step-down adjustment of the bus voltage, which can make the bus voltage higher than the peak value of the AC voltage or lower than the peak value of the AC voltage,
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • the step-up circuit and the step-down circuit are provided with a plurality of semiconductor switches, the semiconductor switches are controlled by a controller, and the controller according to the above collected AC voltage, AC current, DC bus voltage and DC bus current At least one signal modulates the working state of the semiconductor switch, thereby adjusting the working state of the step-up circuit and/or the step-down circuit.
  • the fifth aspect of the present application provides another buck-boost driving method, including: determining the AC voltage input to the driving circuit and the bus voltage of the driving circuit; according to the AC voltage and the bus voltage, The step-down circuit is controlled to operate in a filter mode or a step-down mode, and the totem pole circuit is controlled to operate in a power factor correction mode or a rectification mode.
  • a totem pole circuit and a step-down circuit are provided in the drive circuit, and the totem pole circuit is controlled to work in power factor correction mode or rectification mode according to the AC voltage and the bus voltage, and control
  • the step-down circuit works in the filtering mode or the step-down mode to realize the step-up and step-down adjustment of the bus voltage, which can make the bus voltage higher than the peak value of the AC voltage or lower the bus voltage than the peak value of the AC voltage to increase Motor efficiency and reliability, especially for permanent magnet synchronous motors, can reduce the iron loss of the motor by reducing the bus voltage.
  • a plurality of semiconductor switches are provided in the totem pole circuit and the step-down circuit.
  • the semiconductor switches are controlled by a controller.
  • a signal modulates the working state of the semiconductor switch, and then adjusts the working state of the totem pole circuit and/or the step-down circuit.
  • the sixth aspect of the present application provides yet another buck-boost driving method, including: determining the AC voltage input to the driving circuit and the bus voltage of the driving circuit; according to the AC voltage and the bus voltage, The step-down circuit is controlled to work in a rectification mode or a step-down mode, and the step-up circuit is controlled to work in a step-up mode or a filter mode.
  • a step-down circuit and a step-up circuit are provided in the drive circuit, and the step-down circuit is controlled to operate in a rectification mode or a step-down mode according to the AC voltage and the bus voltage, and The step-up circuit is controlled to work in the step-up mode or the filter mode, and the step-up and step-down adjustment of the bus voltage is realized.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • multiple semiconductor switches are provided in the step-down circuit and the step-up circuit.
  • the semiconductor switches are controlled by a controller. At least one signal modulates the working state of the semiconductor switch, thereby adjusting the working state of the step-down circuit and/or the step-up circuit.
  • the power supply signal generally refers to a signal that flows through the drive circuit and drives the load to operate.
  • the input signal of the bridge circuit is an AC signal
  • the output is a bus DC signal. Therefore, the AC current and AC voltage are collected at the input end of the bridge circuit, and the DC current and DC bus voltage are collected at the output end of the bridge circuit.
  • a seventh aspect of the present application provides an air conditioner, including: a motor; a buck-boost drive circuit as defined in any of the above technical solutions, and the buck-boost drive circuit is configured to control the operation of the motor.
  • the air conditioner includes the buck-boost driving circuit as in any of the above technical solutions. Therefore, the air conditioner includes all the beneficial effects of the buck-boost driving circuit as in any of the above technical solutions. Go into details.
  • the eighth aspect of the present application provides a computer-readable storage medium having a computer program stored on the computer-readable storage medium, and when the computer program is executed, it implements the driving method defined by any one of the above technical solutions.
  • Fig. 1 shows a structural diagram of a buck-boost driving circuit according to an embodiment of the present application
  • Figure 2 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application
  • Fig. 3 shows a structural diagram of a buck-boost driving circuit according to still another embodiment of the present application
  • Fig. 4 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application
  • FIG. 5 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • Fig. 6 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 7 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 8 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 9 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 10 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 11 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 12 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 13 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 14 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 15 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 16 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 17 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 18 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 19 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 20 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 21 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • Fig. 22 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 23 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 24 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 25 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 26 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 27 shows a structural diagram of a buck-boost driving circuit according to another embodiment of the present application.
  • FIG. 28 shows a timing diagram of a buck-boost driving method according to an embodiment of the present application
  • FIG. 29 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 30 shows a timing diagram of a buck-boost driving method according to still another embodiment of the present application.
  • FIG. 31 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 32 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 33 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 34 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 35 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 36 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 37 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 38 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 39 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 40 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 41 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 42 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 43 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 44 shows a schematic flowchart of a buck-boost driving method according to an embodiment of the present application
  • FIG. 45 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 46 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 47 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 48 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 49 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 50 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 51 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 52 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 53 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • Fig. 54 shows a schematic flowchart of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 55 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 56 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 57 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 58 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 59 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 60 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 61 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 62 shows a timing diagram of a buck-boost driving method according to another embodiment of the present application.
  • FIG. 63 shows a schematic flowchart of a buck-boost driving method according to still another embodiment of the present application.
  • Fig. 64 shows a schematic block diagram of an air conditioner according to an embodiment of the present application.
  • Fig. 65 shows a schematic block diagram of a computer-readable storage medium according to an embodiment of the present application.
  • the buck-boost driving circuit, method, air conditioner, and computer-readable storage medium according to some embodiments of the present application are described below with reference to FIGS. 1 to 65.
  • a buck-boost driving circuit including: a boost-type circuit configured to perform a power supply signal Power factor correction processing or rectification processing; a step-down circuit, the input end of the step-down circuit is connected to the output end of the step-up circuit, the step-down circuit includes: a first power tube Q1 and a second The power tube Q2 is connected in series between the high-voltage output terminal and the low-voltage output terminal of the boost circuit.
  • the two ends of the second power tube Q2 lead to a high-voltage bus and a low-voltage bus, wherein the first power is controlled
  • the tube Q1 and the second power tube Q2 are turned on alternately to perform step-down modulation on the bus voltage between the high-voltage bus and the low-voltage bus.
  • the buck-boost adjustment of the bus voltage is realized, which can make the bus voltage higher than the peak value of the AC voltage or lower the bus voltage.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • the step-up circuit and the step-down circuit are provided with a plurality of semiconductor switches, the semiconductor switches are controlled by a controller, and the controller according to the above collected AC voltage, AC current, DC bus voltage and DC bus current At least one signal modulates the working state of the semiconductor switch, thereby adjusting the working state of the step-up circuit and/or the step-down circuit.
  • the boost circuit can be a totem pole circuit, or a combination of a rectifier and a PFC circuit.
  • the power supply signal generally refers to the signal that flows through the drive circuit and drives the load.
  • the input signal of the bridge circuit is an AC signal AC
  • the output is a bus DC signal. Therefore, the AC current and AC voltage are collected at the input end of the bridge circuit, and the DC current and DC bus voltage are collected at the output end of the bridge circuit.
  • the boost circuit of the drive control circuit can also be denoted as a BOOST circuit, and the step-down circuit can also be denoted as a BUCK circuit.
  • the load M can be an inverter IPM and a permanent magnet motor driven by it.
  • the main idea of SVPWM is to use the three-phase symmetrical sine wave voltage power supply as the reference standard for the ideal flux circle of the three-phase symmetrical motor stator, and appropriately switch the different switching modes of the three-phase inverter to form a PWM
  • the wave uses the actual flux linkage vector formed to track its accurate flux linkage circle.
  • the traditional SPWM method starts from the perspective of the power supply to generate a sine wave power supply with adjustable frequency and voltage, while the SVPWM method considers the inverter system and the asynchronous motor as a whole, the model is relatively simple, and it is also convenient for the microprocessor to realize real-time control.
  • the buck-boost driving circuit in the above technical solution provided by this application may also have the following additional technical features:
  • the step-down circuit includes: a filter circuit, the filter circuit is connected in parallel with the second power tube Q2, and the filter circuit is used to counteract the flow through the high-voltage bus and the The power supply signal of the low-voltage bus is filtered.
  • the step-down circuit is configured to include a filter circuit, and the filter circuit performs filtering processing on the DC signal of the bus.
  • the filter circuit performs filtering processing on the DC signal of the bus.
  • the filter circuit includes: a first inductive element L1, and a first end of the first inductive element L1 is connected to one of the first power tube Q1 and the second power tube Q2
  • the common terminal between the first capacitive element C1, the first end of the first capacitive element C1 is connected to the second end of the first inductive element L1, the second end of the first capacitive element C1 Connected to the low-voltage bus.
  • the filter circuit is set to include the first inductive element L1 and the first capacitive element C1, and connected in the above-mentioned manner, that is, the LC filter structure is connected to the load input end to filter out the DC signal carried AC noise to further improve the reliability of load operation.
  • the step-up circuit includes: a second inductive element L2, the second inductive element L2 is configured to access the power supply signal; a bridge circuit, the bridge circuit A power tube is provided in any bridge arm, the input end of the bridge circuit is connected to the second inductive element L2, and the bridge circuit is configured to perform rectification processing or power factor correction on the power supply signal Processing; a second capacitive element C2, the second capacitive element C2 is connected between the two output terminals of the bridge circuit.
  • the bridge circuit includes: a third power tube T1, a fourth power tube T2, a fifth power tube T3, and a sixth power tube T4, the third power tube T1 and the The common end between the fourth power tube T2 is connected to the first end of the second inductive element L2, the first output end of the power supply end is connected to the second end of the second inductive element L2, and the fifth The common terminal between the power tube T3 and the sixth power tube T4 is connected to the second output terminal of the power supply terminal, wherein the common terminal of the third power tube T1 and the fifth power tube T3 serves as the For the high-voltage output terminal, the common terminal of the fourth power tube T2 and the sixth power tube T4 serves as the low-voltage output terminal.
  • the bridge circuit by setting the bridge circuit to specifically include the above four power tubes, and connecting them in the above manner, the AC signal AC can be rectified.
  • the power tubes of the bridge circuit can be rectified according to the specified duty cycle.
  • modulating boost the output bus DC signal is boosted.
  • the controller further includes a controller, which is connected to the control end of the power tube, and the power tube is equipped with an inverter.
  • the first diode is connected in parallel, and the controller drives the bridge circuit to work in diode rectification mode, which specifically includes the following steps: the controller controls the power tubes in the bridge circuit to be turned off, and the anti-parallel connection The first diode rectifies the power supply signal.
  • the controller controls the power tubes in the bridge circuit to be turned off, the anti-parallel first diode rectifies the power supply signal, and the bridge circuit is equivalent to a diode rectifier, Therefore, the rectification process of the AC signal AC is realized.
  • a controller the controller is connected to the control end of the power tube, the power tube is provided with an anti-parallel first diode, the control The driver drives the bridge circuit to work in a synchronous rectification mode, which specifically includes the following steps: when the anti-parallel first diode is turned on, the controller controls the corresponding power tube to turn on with a first duty cycle.
  • the controller controls the corresponding power tube to turn on with the first duty cycle to realize synchronous rectification processing, and the response time is short and High reliability.
  • a controller the controller is connected to the control end of the power tube, the power tube is provided with an anti-parallel first diode, the control The driver drives the bridge circuit to work in a semi-synchronous rectification mode, which specifically includes the following steps: controlling the third power tube T1 and the fifth power tube T3 to turn off, and the anti-parallel first power tube of the fourth power tube T2
  • the controller controls the fourth power tube T2 to turn on
  • the anti-parallel first diode of the sixth power tube T4 turns on
  • the controller controls the The sixth power tube T4 is turned on.
  • the third power tube T1 and the fifth power tube T3 are controlled to be turned off, that is, the first diode of the third power tube T1 in anti-parallel is turned on, and the fifth power tube T3 is turned on. The first diode in anti-parallel is turned on.
  • the controller controls the fourth power tube T2 to be turned on, and the sixth power tube T4 is turned on.
  • the controller controls the sixth power tube T4 to turn on, that is, the fifth power tube T3 and the sixth power tube T4 are used to perform synchronous rectification processing.
  • a controller the controller is connected to the control end of the power tube, the power tube is provided with an anti-parallel first diode, the control The driver drives the bridge circuit to work in a semi-synchronous rectification mode, which specifically includes the following steps: controlling the fourth power tube T2 and the sixth power tube T4 to turn off, and the anti-parallel first power tube T1 of the third power tube
  • the controller controls the third power tube T1 to turn on, and when the anti-parallel first diode of the fifth power tube T3 turns on, the controller controls the The fifth power tube T3 is turned on.
  • the fourth power tube T2 and the sixth power tube T4 are controlled to be turned off, that is, the first diode in the anti-parallel connection of the fourth power tube T2 is turned on, and the anti-parallel of the sixth power tube T4 is turned on.
  • the first diode connected in parallel is turned on.
  • the controller controls the third power tube T1 to turn on, and the anti-parallel first diode of the fifth power tube T3 is turned on.
  • the controller controls the fifth power tube T3 to turn on, that is, the third power tube T1 and the fifth power tube T3 are used for synchronous rectification processing.
  • the controller further includes: a controller connected to the control end of the power tube, and the power tube is equipped with an inverter.
  • the first diode is connected in parallel, and the controller drives the bridge circuit to work in a power factor correction mode, which specifically includes the following steps: the power supply signal is transmitted between the third power tube T1 and the fourth power tube T2 When the common terminal of the fifth power tube T1 and the fourth power tube T2 are turned on alternately with the second duty cycle; the first diode in the anti-parallel connection of the fifth power tube T3 has a current flow When the time is out, the controller controls the fifth power tube T3 to turn on with the third duty cycle, and at the same time, the controller keeps the sixth power tube T4 off; the anti-parallel connection of the sixth power tube T4 When a current flows through the first diode, the controller controls the sixth power tube T4 to turn on with a third duty cycle, and at the same time, the controller keeps the fifth
  • the controller controls the fifth power tube T3 to turn on at a third duty cycle, and at the same time, the control The converter keeps the sixth power tube T4 cut off, and realizes the power factor correction processing of the power supply signal.
  • a controller connected to the control end of the power tube, and the power tube is equipped with an inverter.
  • the first diode is connected in parallel, and the controller drives the bridge circuit to work in a power factor correction mode, which specifically includes the following steps: the power supply signal is transmitted between the fifth power tube T3 and the sixth power tube T4 When the common terminal of the third power tube T3 flows in, the fifth power tube T3 and the sixth power tube T4 are turned on alternately with a fourth duty ratio; the anti-parallel first diode of the third power tube T1 has a current flow When the time is out, the controller controls the third power tube T1 to turn on at the fifth duty cycle, and at the same time, the controller keeps the fourth power tube T2 off; the reverse of the fourth power tube T2 When a current flows through the first diode connected in parallel, the controller controls the fourth power tube T2 to turn on with a fifth duty cycle, and at the same time,
  • the controller controls the fourth power tube T2 to use the fifth duty cycle.
  • the controller keeps the third power tube T1 turned off, and realizes the power factor correction processing of the power supply signal.
  • the controller controls the third power tube T1 to turn on at the fifth duty cycle, and at the same time, The controller keeps the fourth power tube T2 cut off, and realizes the power factor correction processing of the power supply signal.
  • a controller connected to the control end of the power tube, and the second power tube Q2 is set There is an anti-parallel first diode, and the controller drives the step-down circuit to work in a filter mode, which specifically includes the following steps: the controller controls the first power tube Q1 to be turned on, and the controller The second power tube Q2 is controlled to be turned off or alternately turned on with the first power tube Q1, and the filter circuit performs filtering processing on the power supply signal.
  • the second power tube Q2 is controlled to be turned off by the controller, and both the second power tube Q2 and its anti-parallel first diode are turned off, or the second power tube Q2 and the first power tube Q2 are turned off.
  • Q1 is turned on alternately, and at this time, only the power supply signal is filtered by the filter circuit to filter out the interference of the noise signal to the load.
  • a controller connected to the control end of the power tube, and the controller drives the step-down circuit to work in a step-down mode, specifically including the following Step:
  • the controller controls the first power tube Q1 to be turned on with a sixth duty cycle, and at the same time, the controller controls the second power tube Q2 and the first power tube Q1 to alternately turn on.
  • the controller controls the first power tube Q1 to turn on at a sixth duty cycle, and at the same time, the controller controls the second power tube Q2 and the first power tube Q1.
  • Alternate conduction that is, the first power tube Q1 and the second power tube Q2 are used to modulate and reduce the voltage of the bus DC signal, so as to improve the efficiency of the load and, in addition, help reduce the iron loss of the motor.
  • the freewheeling power tubes of the boost circuit are the fifth power tube T3 and the third power tube T1, which are replaced by the uncontrolled diode D3 and the uncontrolled diode D1, respectively, and no modulation control is required.
  • the above-mentioned power tube and switch tube can be Si material-based MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor, metal oxide semiconductor field effect transistor, MOSFET for short), SiC material-based MOSFET or GaN material-based MOSFET, and
  • the four power tubes of the bridge circuit and the second power tube Q2 need to be provided with anti-parallel first diodes or parasitic diodes, and the first power tube Q1 may not be provided with anti-parallel first diodes.
  • another buck-boost driving circuit including: a totem pole circuit configured to perform power on a power supply signal Factor correction processing or rectification processing; a step-down circuit, the input end of the step-down circuit is connected to the output end of the totem pole circuit, the step-down circuit includes: a first power tube Q1 and a second power tube Q2 is connected in series between the high-voltage output terminal and the low-voltage output terminal of the totem pole circuit.
  • the two ends of the second power tube Q2 lead to a high-voltage bus and a low-voltage bus, wherein the first power tube Q1 and The second power tube Q2 is turned on alternately, the bus voltage between the high-voltage bus and the low-voltage bus decreases as the load operation time increases, and the step-down circuit is configured to perform step-down processing on the power supply signal Or filter processing.
  • the buck-boost adjustment of the bus voltage is realized, which can make the bus voltage higher than the peak value of the AC voltage or lower the bus voltage
  • the peak value of AC voltage is used to improve the efficiency and reliability of the motor.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • a plurality of semiconductor switches are provided in the totem pole circuit and the step-down circuit.
  • the semiconductor switches are controlled by a controller.
  • a signal modulates the working state of the semiconductor switch, and then adjusts the working state of the totem pole circuit and/or the step-down circuit.
  • the power supply signal generally refers to the signal that flows through the drive circuit and drives the load.
  • the input signal of the bridge circuit is an AC signal AC
  • the output is a bus DC signal. Therefore, the AC current and AC voltage are collected at the input end of the bridge circuit, and the DC current and DC bus voltage are collected at the output end of the bridge circuit.
  • the totem pole circuit of the drive control circuit can also be referred to as the BOOST circuit, and the step-down circuit can also be referred to as the BUCK circuit.
  • the load M may be an inverter IPM and a permanent magnet motor driven by it.
  • the main idea of SVPWM is to use the three-phase symmetrical sine wave voltage power supply as the reference standard for the ideal flux circle of the three-phase symmetrical motor stator, and appropriately switch the different switching modes of the three-phase inverter to form a PWM
  • the wave uses the actual flux linkage vector formed to track its accurate flux linkage circle.
  • the traditional SPWM method starts from the perspective of the power supply to generate a sine wave power supply with adjustable frequency and voltage, while the SVPWM method considers the inverter system and the asynchronous motor as a whole, the model is relatively simple, and it is also convenient for the microprocessor to realize real-time control.
  • the buck-boost driving circuit in the above technical solution provided by this application may also have the following additional technical features:
  • the step-down circuit includes: a filter circuit, the filter circuit is connected in parallel with the second power tube Q2, and the filter circuit is used to counteract the flow through the high-voltage bus and the The power supply signal of the low-voltage bus is filtered.
  • the step-down circuit is configured to include a filter circuit, and the filter circuit performs filtering processing on the DC signal of the bus.
  • the filter circuit performs filtering processing on the DC signal of the bus.
  • the filter circuit includes: a first inductive element L1, and a first end of the first inductive element L1 is connected to one of the first power tube Q1 and the second power tube Q2
  • the common terminal between the first capacitive element C1, the first end of the first capacitive element C1 is connected to the second end of the first inductive element L1, the second end of the first capacitive element C1 Connected to the low-voltage bus.
  • the filter circuit is set to include the first inductive element L1 and the first capacitive element C1, and connected in the above-mentioned manner, that is, the LC filter structure is connected to the load input end to filter out the DC signal carried AC noise to further improve the reliability of load operation.
  • the totem pole circuit includes: a second inductive element L2, the second inductive element L2 is configured to access the power supply signal; a bridge circuit, any of the bridge circuit A power tube is provided in a bridge arm, the input end of the bridge circuit is connected to the second inductive element L2, and the bridge circuit is configured to perform power factor correction processing or rectification processing on the power supply signal ; A second capacitive element C2, the second capacitive element C2 is connected between the two output terminals of the bridge circuit.
  • the third power tube T1, the fourth power tube T2, the fifth power tube T3, and the sixth power tube T4 between the third power tube T1 and the fourth power tube T2 Is connected to the first end of the second inductive element L2, the first output end of the power supply end is connected to the second end of the second inductive element L2, and the fifth power tube T3 is connected to the first end of the second inductive element L2.
  • the common terminal between the six power tubes T4 is connected to the second output terminal of the power supply terminal, wherein the common terminal of the third power tube T1 and the fifth power tube T3 serves as the high-voltage output terminal, and the first The common terminal of the four power tube T2 and the sixth power tube T4 serves as the low-voltage output terminal.
  • the bridge circuit by setting the bridge circuit to specifically include the above four power tubes, and connecting them in the above manner, the AC signal AC can be rectified.
  • the power tubes of the bridge circuit can be rectified according to the specified duty cycle.
  • modulating boost the output bus DC signal is boosted.
  • any of the above technical solutions it further includes: a controller connected to the control end of the power tube, and the power tube is equipped with an inverter.
  • the first diode is connected in parallel, and the controller drives the bridge circuit to work in diode rectification mode, which specifically includes the following steps: the controller controls the power tubes in the bridge circuit to be turned off, and the anti-parallel connection The first diode rectifies the power supply signal.
  • the controller controls the power tubes in the bridge circuit to be turned off, the anti-parallel first diode rectifies the power supply signal, and the bridge circuit is equivalent to a diode rectifier, Therefore, the rectification process of the AC signal AC is realized.
  • a controller the controller is connected to the control end of the power tube, the power tube is provided with an anti-parallel first diode, the control The driver drives the bridge circuit to work in a synchronous rectification mode, which specifically includes the following steps: when the anti-parallel first diode is turned on, the controller controls the corresponding power tube to turn on with a first duty cycle.
  • the controller controls the corresponding power tube to turn on with the first duty cycle to realize synchronous rectification processing, and the response time is short and High reliability.
  • a controller the controller is connected to the control end of the power tube, the power tube is provided with an anti-parallel first diode, the control The driver drives the bridge circuit to work in a semi-synchronous rectification mode, which specifically includes the following steps: controlling the third power tube T1 and the fourth power tube T2 to turn off, and the fifth power tube T3 is connected in anti-parallel to the first
  • the controller controls the fifth power tube T3 to turn on
  • the anti-parallel first diode of the sixth power tube T4 turns on
  • the controller controls the The sixth power tube T4 is turned on.
  • the controller controls the fifth power tube T3 to be turned on, and the sixth power tube T4 is turned on.
  • the controller controls the sixth power tube T4 to turn on, that is, the fifth power tube T3 and the sixth power tube T4 are used to perform synchronous rectification processing.
  • a controller the controller is connected to the control end of the power tube, the power tube is provided with an anti-parallel first diode, the control The driver drives the bridge circuit to work in a semi-synchronous rectification mode, which specifically includes the following steps: controlling the fifth power tube T3 and the sixth power tube T4 to turn off, and the anti-parallel first power tube of the third power tube T1
  • the controller controls the third power tube T1 to turn on
  • the anti-parallel first diode of the fourth power tube T2 turns on
  • the controller controls the The fourth power tube T2 is turned on.
  • the fifth power tube T3 and the sixth power tube T4 are controlled to be turned off, that is, the first diode in the anti-parallel connection of the fifth power tube T3 is turned on, and the anti-parallel of the sixth power tube T4 is turned on.
  • the first diode connected in parallel is turned on.
  • the controller controls the third power tube T1 to be turned on, and the anti-parallel first diode of the fourth power tube T2 is turned on.
  • the controller controls the fourth power tube T2 to turn on, that is, the third power tube T1 and the fourth power tube T2 are used for synchronous rectification processing.
  • the controller further includes: a controller connected to the control end of the power tube, and the power tube is equipped with an inverter.
  • the first diode is connected in parallel, and the controller drives the bridge circuit to work in a power factor correction mode, which specifically includes the following steps: the power supply signal is transmitted between the third power tube T1 and the fourth power tube T2 When the common terminal of the fifth power tube T1 and the fourth power tube T2 are turned on alternately with the second duty cycle; the first diode in the anti-parallel connection of the fifth power tube T3 has a current flow When the time is out, the controller controls the fifth power tube T3 to turn on with the third duty cycle, and at the same time, the controller keeps the sixth power tube T4 off; the anti-parallel connection of the sixth power tube T4 When a current flows through the first diode, the controller controls the sixth power tube T4 to turn on with a third duty cycle, and at the same time, the controller keeps the fifth
  • the controller controls the fifth power tube T3 to turn on at a third duty cycle, and at the same time, the control The converter keeps the sixth power tube T4 cut off, and realizes the power factor correction processing of the power supply signal.
  • a controller connected to the control end of the power tube, and the power tube is equipped with an inverter.
  • the first diode is connected in parallel, and the controller drives the bridge circuit to work in a power factor correction mode, which specifically includes the following steps: the power supply signal is transmitted between the fifth power tube T3 and the sixth power tube T4 When the common terminal of the third power tube T3 flows in, the fifth power tube T3 and the sixth power tube T4 are turned on alternately with a fourth duty ratio; the anti-parallel first diode of the third power tube T1 has a current flow When the time is out, the controller controls the third power tube T1 to turn on at the fifth duty cycle, and at the same time, the controller keeps the fourth power tube T2 off; the reverse of the fourth power tube T2 When a current flows through the first diode connected in parallel, the controller controls the fourth power tube T2 to turn on with a fifth duty cycle, and at the same time,
  • the controller controls the fourth power tube T2 to use the fifth duty cycle.
  • the controller keeps the third power tube T1 turned off, and realizes the power factor correction processing of the power supply signal.
  • the controller controls the third power tube T1 to turn on at the fifth duty cycle, and at the same time, The controller keeps the fourth power tube T2 cut off, and realizes the power factor correction processing of the power supply signal.
  • a controller connected to the control end of the power tube, and the second power tube Q2 is set There is an anti-parallel first diode, and the controller drives the step-down circuit to work in a filter mode, which specifically includes the following steps: the controller controls the first power tube Q1 to be turned on, and the controller The second power tube Q2 is controlled to be turned off or alternately turned on with the first power tube Q1, and the filter circuit performs filtering processing on the power supply signal.
  • the second power tube Q2 is controlled to be turned off by the controller, and both the second power tube Q2 and its anti-parallel first diode are turned off, or the second power tube Q2 and the first power tube Q2 are turned off.
  • Q1 is turned on alternately, and at this time, only the power supply signal is filtered by the filter circuit to filter out the interference of the noise signal to the load.
  • a controller connected to the control end of the power tube, and the controller drives the step-down circuit to work in a step-down mode, specifically including the following Step:
  • the controller controls the first power tube Q1 to be turned on with a sixth duty cycle, and at the same time, the controller controls the second power tube Q2 and the first power tube Q1 to alternately turn on.
  • the controller controls the first power tube Q1 to turn on at a sixth duty cycle, and at the same time, the controller controls the second power tube Q2 and the first power tube Q1.
  • Alternate conduction that is, the first power tube Q1 and the second power tube Q2 are used to modulate and reduce the voltage of the bus DC signal, so as to improve the efficiency of the load and, in addition, help reduce the iron loss of the motor.
  • the side arms of the low-frequency switch control of the totem pole circuit are the fifth power tube T3 and the sixth power tube T4, which are replaced by the uncontrolled diode D3 and the uncontrolled diode D4, respectively, and no modulation control is required.
  • the above-mentioned power tube and switch tube can be Si material-based MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor, metal oxide semiconductor field effect transistor, MOSFET for short), SiC material-based MOSFET or GaN material-based MOSFET, and ,
  • MOSFET Metal-Oxide-Semiconductor Field-Effect Transistor, metal oxide semiconductor field effect transistor, MOSFET for short
  • SiC material-based MOSFET or GaN material-based MOSFET Si material-based MOSFET
  • the four power tubes of the bridge circuit and the second power tube Q2 need to be provided with anti-parallel first diodes, and the first power tube Q1 may not be provided with anti-parallel first diodes.
  • yet another buck-boost driving circuit including a buck-type circuit 100, the buck-type circuit 100 including a bridge circuit, A power tube is provided in any bridge arm of the bridge circuit, and the step-down circuit 100 is configured to access the power supply signal input from the power supply terminal; the step-up circuit 200, the step-up circuit The input end of 200 is connected to the output end of the step-down circuit 100, and the step-up circuit 200 is configured to boost the power supply signal; the seventh power tube Q11 is connected to the two ends of the bridge circuit. There are two output terminals connected to the two input terminals of the boost circuit, and the seventh power tube Q11 is configured to be capable of freewheeling the boost circuit.
  • the step-down circuit 100 and the step-up circuit 200 are provided in the drive circuit to realize the step-down adjustment of the bus voltage, which can make the bus voltage higher than the peak value of the AC voltage or make the bus The voltage is lower than the peak value of the AC voltage to improve the efficiency and reliability of the motor.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • the power supply signal generally refers to the signal that flows through the drive circuit and drives the load M to operate.
  • the input signal of the bridge circuit is an AC signal AC
  • the output is a bus DC signal. Therefore, the AC current and AC voltage are collected at the input end of the bridge circuit, and the DC current and DC bus voltage are collected at the output end of the bridge circuit.
  • the step-down circuit 100 and the step-up circuit 200 are provided with a plurality of semiconductor switches, the semiconductor switches are controlled by a controller, and the controller is based on the collected AC voltage, AC current, DC bus voltage and DC bus current. At least one signal in modulates the working state of the semiconductor switch, thereby adjusting the working state of the buck circuit 100 and/or the boost circuit 200.
  • the step-down circuit 100 of the drive control circuit can also be referred to as a bridgeless BUCK circuit
  • the step-up circuit 200 can also be referred to as a BOOST circuit.
  • the output of the bridgeless BUCK circuit is directly connected to the input of the BOOST circuit.
  • the input of the bridgeless BUCK circuit is connected to a single-phase AC power supply, and the output of the BOOST circuit is connected to the load M.
  • the load M may be an inverter IPM and a permanent magnet motor driven by it.
  • the high voltage output end of the bridge circuit is connected to one end of the third inductive element L3, the low voltage output end of the bridge circuit is connected to the low voltage input end of the BOOST circuit, and the drain of the seventh power tube Q11 is connected to one end of the third inductive element L3, The source of the seventh power tube Q11 is connected to the low-voltage output of the bridge circuit.
  • the main idea of SVPWM is to use the three-phase symmetrical sine wave voltage power supply as the reference standard for the ideal flux circle of the three-phase symmetrical motor stator, and appropriately switch the different switching modes of the three-phase inverter to form a PWM
  • the wave uses the actual flux linkage vector formed to track its accurate flux linkage circle.
  • the traditional SPWM method starts from the perspective of the power supply to generate a sine wave power supply with adjustable frequency and voltage, while the SVPWM method considers the inverter system and the asynchronous motor as a whole, the model is relatively simple, and it is also convenient for the microprocessor to realize real-time control.
  • the buck-boost driving circuit in the above technical solution provided by this application may also have the following additional technical features:
  • the bridge circuit includes: a first unidirectional conducting tube T11, an eighth power tube T12, a second unidirectional conducting tube T13, and a ninth power tube.
  • Tube T14, the common end between the first unidirectional guide tube T11 and the eighth power tube T12 is connected to the first output end of the power supply terminal, and the second unidirectional guide tube T13 is connected to the ninth power tube T13.
  • the common terminal between the power tubes T14 is connected to the second output terminal of the power supply terminal, and the common terminal of the first unidirectional conducting tube T11 and the second unidirectional conducting tube T13 serves as the high-voltage output of the bridge circuit
  • the common terminal of the eighth power tube T12 and the ninth power tube T14 serves as the low-voltage output terminal of the bridge circuit, wherein the first unidirectional conducting tube T11 and the second unidirectional conducting tube T13 Both are turned off, and the seventh power tube Q11 performs freewheeling on the boost circuit.
  • the bridge circuit by setting the bridge circuit to specifically include the above four power tubes, and connecting them in the above manner, the AC signal AC can be rectified.
  • a seventh power is provided at the output end of the bridge circuit.
  • the seventh power tube Q11 When the seventh power tube Q11 is turned on, the rectified DC signal cannot be transmitted to the next step-up circuit 200.
  • the seventh power tube Q11 When the seventh power tube Q11 is turned off, the DC signal output by the bridge circuit is transmitted to the step-up circuit.
  • the circuit 200 can continue to perform modulation and boosting via the boost circuit 200.
  • the first unidirectional conducting tube T11 and the second unidirectional conducting tube T13 chop the power supply signal to perform step-down modulation on the bus voltage.
  • a controller connected to the control end of the power tube, and the eighth power tube T12 is provided with an inverter A second diode connected in parallel, the ninth power tube T14 is provided with a third diode connected in anti-parallel, and the controller drives the bridge circuit to work in a diode rectification mode, which specifically includes the following steps: The controller controls both the eighth power tube T12 and the ninth power tube T14 to turn off, the second diode and the third diode rectify the power supply signal, wherein the first The drain voltage of the one-way conduction transistor T11 is higher than the source voltage, the first one-way conduction transistor T7 is turned on, the drain voltage of the second one-way conduction transistor T13 is higher than the source voltage, and the second one The one-way guide tube T13 is turned on.
  • the controller drives the bridge circuit for rectification, by controlling both the eighth power tube T12 and the ninth power tube T14 to turn off, the second diode and the third second The pole tube rectifies the power supply signal, wherein the drain voltage of the first one-way conduction transistor T11 is higher than the source voltage, the first one-way conduction transistor T11 is turned on, and the second one-way conduction transistor T11 is turned on.
  • the drain voltage of the tube T13 is higher than the source voltage, and the second unidirectional conduction tube T13 is turned on.
  • both the ninth power tube T14 and the eighth power tube T12 can be replaced by diodes.
  • the controller drives the bridge circuit to work in a synchronous rectification mode, which specifically includes: the first single The drain voltage of the conduction transistor T11 is higher than the source voltage, the first one-way conduction transistor T11 is turned on, and at the same time, the ninth power transistor T14 is turned on, and the drain of the second one-way conduction transistor T13 When the voltage is higher than the source voltage, the second unidirectional conduction transistor T13 is turned on, and at the same time, the eighth power transistor T12 is turned on.
  • the bridge circuit is driven by the controller to work in the synchronous rectification mode, that is, the drain voltage of the first unidirectional conducting transistor T11 is higher than the source voltage, and the first unidirectional conducting transistor T11 At the same time, the ninth power tube T14 is turned on. At this time, the power supply signal is output through the first unidirectional conductive tube T11 and the ninth power tube T4, and the response time is short and the reliability is high.
  • the drain voltage of the second one-way conduction transistor T13 is higher than the source voltage, the second one-way conduction transistor T13 is turned on, and at the same time, the eighth power transistor T12 is turned on.
  • the power tube T12 and the second unidirectional guide tube T13 output power supply signals with short response time and high reliability.
  • a controller connected to the control end of the power tube, and the eighth power tube T12 is provided with an inverter A second diode connected in parallel, the ninth power tube T14 is provided with a third diode connected in anti-parallel, and the controller drives the bridge circuit to work in a diode rectification and step-down mode, which specifically includes: the control The device controls the eighth power tube T12 and the ninth power tube T14 to be turned off, the second diode and the third diode rectify the power supply signal; the first unidirectional conduction The drain voltage of the transistor T11 is higher than the source voltage, the controller triggers the first one-way conduction transistor T11 to turn on or off according to the first duty cycle, and the drain voltage of the second one-way conduction transistor T13 Above the source voltage, the controller triggers the second unidirectional conduction transistor T13 to be turned on or off according to the second duty cycle.
  • the controller drives the bridge circuit to work in a diode rectification and step-down mode.
  • the controller controls the eighth power tube T12 and the ninth power tube T14 Both are off, the second diode and the third diode rectify the power supply signal, the drain voltage of the first unidirectional conducting transistor T11 is higher than the source voltage, and the controller triggers
  • the first one-way conduction transistor T11 is turned on or off according to a first duty cycle
  • the drain voltage of the second one-way conduction transistor T13 is higher than the source voltage
  • the controller triggers the second one-way conduction
  • the through tube T13 is turned on or off according to the second duty ratio.
  • the first unidirectional guide tube T11 and the second unidirectional guide tube T13 work in sequence within two half cycles of the AC voltage.
  • the first unidirectional guide tube T11 and the second unidirectional guide tube T11 A dead time is set for the switching period between the through-tubes T13.
  • the controller can trigger the seventh power tube Q11 to perform step-down modulation with a specified duty cycle.
  • the step-up circuit 200 works in a filtering mode without performing Boost modulation to improve the efficiency of the drive circuit.
  • a controller connected to the control end of the power tube, and the eighth power tube T12 is provided with an inverter A second diode in parallel, the ninth power tube T14 is provided with a third diode in anti-parallel, and the controller drives the bridge circuit to work in a synchronous rectification and step-down mode, which specifically includes: the first The drain voltage of a unidirectional conduction transistor T11 is higher than the source voltage, the ninth power transistor T14 is turned on, and at the same time, the controller controls the first unidirectional conduction transistor T11 to be turned on according to a third duty cycle Or cut off, the drain voltage of the second unidirectional conduction transistor T13 is higher than the source voltage, the eighth power transistor T12 is turned on, and at the same time, the controller controls the second unidirectional conduction transistor T13 according to the first The four duty cycle turns on or off.
  • the controller drives the bridge circuit to work in a synchronous rectification and step-down mode, the drain voltage of the first unidirectional conducting transistor T11 is higher than the source voltage, and the ninth power transistor T14 is turned on, and at the same time, the controller controls the first one-way conduction transistor T11 to turn on or off according to a third duty ratio, and the drain voltage of the second one-way conduction transistor T13 is higher than the source voltage,
  • the eighth power tube T12 is turned on, and at the same time, the controller controls the second one-way conduction tube T13 to be turned on or off according to a fourth duty ratio.
  • the ninth power tube T14 is turned on, and the first unidirectional conduction tube T11 starts to modulate.
  • the eighth power transistor T12 is turned on, and the second unidirectional conduction transistor T13 starts to modulate.
  • first unidirectional guide tube T11 and the second unidirectional guide tube T13 work in sequence within two half cycles of the AC voltage.
  • first unidirectional guide tube T11 and the second unidirectional guide tube T11 A dead time is set for the switching period between the through-tubes T13.
  • the eighth power tube T12 and the ninth power tube T14 work sequentially in two half cycles of the AC voltage.
  • the switching period between the eighth power tube T12 and the ninth power tube T14 There is a dead time set.
  • one of the first unidirectional conducting transistor T11 and the ninth power transistor T14 is a reverse blocking switch or an insulated gate gate transistor
  • the other one of the first unidirectional conducting tube T11 and the ninth power tube T14 is an uncontrolled diode or a metal oxide semiconductor tube
  • the eighth power tube T12 and the second unidirectional conducting tube are One of the power tubes in the tube T13 is a reverse blocking switch tube or an insulated gate gate transistor, and the other power tube in the eighth power tube T12 and the second one-way conducting tube T13 is an uncontrolled diode or a metal Oxide semiconductor tube.
  • one of the eighth power tube T12 and the ninth power tube T14 can be set to be a reverse blocking switch tube or an insulated gate gate transistor, and the other is an uncontrolled diode or a metal oxide semiconductor. Tube, is conducive to reducing the power consumption and reliability of the drive circuit.
  • the reverse blocking switch tube includes: a first N-channel metal oxide semiconductor tube and a second N-channel metal oxide semiconductor tube Tube, the drains of the two N-channel metal oxide semiconductor tubes are connected; a comparator, the source of the first N-channel metal oxide semiconductor tube is connected to the first input terminal of the comparator, The source of the second N-channel metal oxide semiconductor tube is connected to the second input of the comparator; a controller, the input of the controller is connected to the output of the comparator, and the control The output terminal of the device is connected to the gate of the N-channel metal oxide semiconductor tube.
  • the key components of the reverse blocking switch are a comparator and two metal oxide semiconductor tubes connected in reverse series, wherein the source of the first N-channel metal oxide semiconductor tube is connected to the The first input terminal of the comparator, the source of the second N-channel metal oxide semiconductor tube is connected to the second input terminal of the comparator, and the conduction of the metal oxide semiconductor tube is controlled by the output result of the comparator Or cut off.
  • a reverse blocking switch is set to overcome the problems of large diode voltage drop and large power consumption, and the response efficiency is high.
  • the reverse blocking switch tube includes: a first P channel metal oxide semiconductor tube and a second P channel metal oxide semiconductor tube, two of the P channel The source of the metal oxide semiconductor tube is connected; a comparator, the drain of the first P-channel metal oxide semiconductor tube is connected to the first input terminal of the comparator, and the second P-channel metal is oxidized The drain of the semiconductor transistor is connected to the second input of the comparator; a controller, the input of the controller is connected to the output of the comparator, and the output of the controller is connected to the P The gate of the channel metal oxide semiconductor tube.
  • the above two P-type MOS switch tubes are connected in reverse series and the anodes of the anti-parallel diodes are connected, and a comparator and a driver are added.
  • the comparator compares the voltages of the upper and lower ends of the two MOS transistors. When the voltage at the upper end A is higher than the voltage at the lower end B, the driver is turned off, and the MOS transistor is in the off state. When the voltage at the lower end B is higher than the voltage at the upper end A, the driver is enabled to enable the switch It is controlled by a control signal to achieve turn-on and turn-off.
  • the key components of the reverse blocking switch are a comparator and two metal oxide semiconductor tubes connected in reverse series, wherein the source of the first P-channel metal oxide semiconductor tube is connected to the The first input terminal of the comparator, the source of the second P-channel metal oxide semiconductor tube is connected to the second input terminal of the comparator, and the conduction of the metal oxide semiconductor tube is controlled by the output result of the comparator Or cut off.
  • a reverse blocking switch is set to overcome the problems of large diode voltage drop and large power consumption, and the response efficiency is high.
  • the above-mentioned two N-type MOS switch tubes are connected in reverse series and the negative electrodes of the anti-parallel diodes are connected, and a comparator and a driver are added.
  • the comparator compares the voltages of the upper and lower ends of the two MOS transistors. When the voltage at the upper end A is higher than the voltage at the lower end B, the driver is turned off and the MOS transistor is in the off state; when the voltage at the lower end B is higher than the voltage at the upper end A, the driver is enabled so that the switch can be It is controlled by a control signal to achieve turn-on and turn-off.
  • the reverse blocking switch tube includes a diode D0 and a metal oxide semiconductor tube connected in series, the metal oxide semiconductor tube is provided with an anti-parallel diode, and the diode D0 The conduction direction of is opposite to the conduction direction of the anti-parallel diode.
  • the reverse blocking switch tube includes a diode D0 connected in series and a metal oxide semiconductor tube.
  • the metal oxide semiconductor tube is provided with an anti-parallel diode.
  • the conduction direction of the anti-parallel diode is opposite.
  • the series diode D0 and the anti-parallel diode are also cut off due to the opposite conduction direction. Based on this, it can overcome the large voltage drop of the diode and the work Problems such as high consumption and high response efficiency.
  • the N-channel metal oxide semiconductor tube includes a gate G, a source S, and a drain D.
  • the source S is connected to the anode of the diode D0.
  • the boost circuit 200 includes: a third inductive element L3, the first end of the third inductive element L3 is connected to the high-voltage output end of the bridge circuit;
  • the tenth power tube Q13 is connected between the second end of the third inductive element L3 and the low-voltage output end of the bridge circuit;
  • the eleventh power tube Q12 is connected to the second end of the third inductive element L3
  • the controller is connected to the tenth power tube The control terminal of Q13 and the control terminal of the eleventh power tube Q12.
  • the controller controls the boost circuit 200 to operate in a boost mode, which specifically includes: the controller according to the high-voltage output terminal and the The given voltage value corresponding to the bus voltage between the low-voltage output terminals and the bus voltage determine a fifth duty cycle, and the controller controls the tenth power tube Q13 to be turned on or When turned off, the eleventh power tube Q12 and the tenth power tube Q13 are turned on alternately or remain turned off.
  • the step-up circuit 200 is configured to include a third inductive element L3, a tenth power tube Q13, and an eleventh power tube Q12, wherein the controller is based on the high-voltage output terminal and the The given voltage value corresponding to the bus voltage between the low-voltage output terminals and the bus voltage determine a fifth duty cycle, and the controller controls the tenth power tube Q13 to be turned on or off according to the fifth duty cycle.
  • the booster circuit 200 boosts and modulates the DC voltage of the bus to meet the operational requirements and reliability of the load M.
  • the boost circuit 200 includes: a third inductive element L3, the first end of the third inductive element L3 is connected to the high-voltage output end of the bridge circuit;
  • the tenth power tube Q13 is connected between the second end of the third inductive element L3 and the low-voltage output end of the bridge circuit;
  • the eleventh power tube Q12 is connected to the second end of the third inductive element L3 Between the first end of the third capacitive element C3 and the first end of the third capacitive element C3, the second end of the third capacitive element C3 is connected to the low-voltage output end;
  • a controller the controller is connected to the tenth power tube
  • the control terminal of Q13 and the control terminal of the eleventh power tube Q12, the controller controlling the boost circuit 200 to operate in a filtering mode specifically includes: the controller controlling the eleventh power tube Q12 Turning on, the controller controls the tenth power tube Q13 to turn off.
  • the step-up circuit 200 is configured to include a third inductive element L3, a tenth power tube Q13, and an eleventh power tube Q12, wherein the controller controls the eleventh power tube Q12 When it is turned on, the controller controls the tenth power tube Q13 to turn off.
  • the boost circuit 200 performs through filtering on the DC voltage of the bus to reduce the ripple noise in the driving circuit.
  • the BOOST circuit includes a tenth power tube Q13, an eleventh power tube Q12, a third inductive element L3, and a third capacitive element C3.
  • the source of the eleventh power tube Q12 and the drain of the tenth power tube Q13 are connected One end of the third inductive element L3, the source of the tenth power tube Q13 is connected to the low voltage output of the bridge circuit and the negative electrode of the first electrolytic capacitor, and the drain of the eleventh power tube Q12 is connected to the positive electrode of the third capacitive element C3 Connected.
  • the first unidirectional conduction transistor T11 and the second unidirectional conduction transistor T13 can be reverse blocking power switches, or IGBT (Insulated Gate Bipolar Transistor, insulated gate bipolar transistor) without anti-parallel diode or reverse
  • the circuit module implemented by blocking the power switch tube, the eighth power tube T12, the ninth power tube 14, the seventh power tube Q11 and the eleventh power tube Q12 are bidirectional power switches, which can be MOSFETs based on Si materials ( Metal-Oxide-Semiconductor Field-Effect Transistor, metal oxide semiconductor field-effect transistor, MOSFET for short), MOSFET based on SiC material or MOSFET based on GaN material, the tenth power transistor Q3 can be a power switch or an IGBT, It can also be a MOSFET based on Si material, a MOSFET based on SiC material, or a MOSFET based on GaN material.
  • the eighth power tube T12, the ninth power tube T14, the first power tube Q1, the tenth power tube Q13, and the eleventh power tube Q12 need to have anti-parallel diodes, such as parasitic diodes or external parallel diodes.
  • the conducting tube T11 nor the second unidirectional conducting tube T13 has anti-parallel diodes.
  • the eighth power tube T12, the tenth power tube Q13, and the seventh power tube Q11 of the bridgeless BOOST circuit can be replaced with uncontrolled diodes, which do not need to be turned on or off.
  • the tenth power tube Q13 of the bridgeless BOOST circuit can be replaced with an uncontrolled diode, without control.
  • the use of uncontrolled diodes has lower cost, but will increase diode conduction loss, especially in the case of low and medium load operation, the diode conduction voltage drop is greater than the MOSFET conduction voltage drop.
  • the first unidirectional guide tube T11 and the ninth power tube T14 are a group
  • the eighth power tube T2 and the second unidirectional guide tube T13 are a group.
  • the above-mentioned control logic is based on that the first unidirectional conducting tube T11 is a reverse blocking power switch, and the ninth power tube T14 is a bidirectional conducting power switch. As shown in Figure 22 and Figure 24, if the ninth power tube T14 is a reverse blocking power switch tube and the first unidirectional guide tube T11 is a bidirectional power switch tube, then the first unidirectional guide tube T11 and the first unidirectional guide tube T11 are controlled. The control logic of the nine power tube T14 is reversed.
  • the above-mentioned control logic is based on that the second unidirectional conducting tube T13 is a reverse blocking power switch, and the eighth power tube T12 is a bidirectional conducting power switch. As shown in Figure 23 and Figure 24, if the eighth power tube T12 is a reverse blocking power switch tube and the second unidirectional conducting tube T13 is a bidirectional conducting power switch tube, then the eighth power tube T12 and the second single conducting tube are controlled. The control logic of the guide tube T13 is reversed.
  • a buck-boost driving method including: step S302, determining the AC voltage input to the driving circuit and the bus voltage of the driving circuit Step S304, according to the AC voltage and the bus voltage, control the step-down circuit to operate in a filter mode or a step-down mode, and control the step-up circuit to operate in a power factor correction mode or a rectification mode.
  • a step-up circuit and a step-down circuit are provided in the drive circuit, and according to the AC voltage and the bus voltage, the step-up circuit is controlled to operate in a rectification mode or a power factor correction mode, And controlling the step-down circuit to work in the step-down mode or the filtering mode to achieve the step-up and step-down adjustment of the bus voltage, which can make the bus voltage higher than the peak value of the AC voltage or lower the bus voltage than the peak value of the AC voltage.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • the power supply signal generally refers to the signal that flows through the drive circuit and drives the load.
  • the input signal of the bridge circuit is an AC signal
  • the output is a bus DC signal. Therefore, the AC current and AC voltage are collected at the input end of the bridge circuit, and the DC current and DC bus voltage are collected at the output end of the bridge circuit.
  • the step-up circuit and the step-down circuit are provided with a plurality of semiconductor switches, the semiconductor switches are controlled by a controller, and the controller according to the above collected AC voltage, AC current, DC bus voltage and DC bus current At least one signal modulates the working state of the semiconductor switch, thereby adjusting the working state of the step-up circuit and/or the step-down circuit.
  • the step-down circuit is controlled to operate in a filter mode or a step-down mode
  • the step-up circuit is controlled to perform power factor correction Mode or rectification mode operation, specifically including: determining the given voltage value corresponding to the bus voltage; comparing the magnitude relationship between the given voltage value and the AC voltage; according to the difference between the given voltage value and the AC voltage
  • the magnitude relationship between the step-down circuit is controlled to operate in the filter mode or the step-down mode
  • the step-up circuit is controlled to operate in the power factor correction mode or the rectification mode.
  • the step-down circuit is controlled to operate in the filter mode or the step-down mode, and the step-up circuit is controlled Work in power factor correction mode or rectification mode.
  • the step-up circuit works in the rectification mode, or the step-up circuit works in the power factor correction mode
  • the step-down circuit works in a filter mode
  • the step-down circuit works in a filter mode.
  • the step-up circuit can work in a rectifier mode.
  • the step-down circuit is controlled to operate in a filter mode or a step-down mode, and the step-up circuit is controlled to perform power factor correction Mode or rectification mode operation, specifically including: determining the product of the effective value of the AC voltage and the first voltage coefficient, and recording the product as the first voltage sampling value; detecting that the first voltage sampling value is greater than or equal to The voltage set value corresponding to the bus voltage is detected, and the instantaneous value of the AC voltage is detected; the instantaneous value of the AC voltage is detected to be less than the voltage set value corresponding to the bus voltage, and the step-up circuit is controlled to work in rectification mode , Control the step-down circuit to work in the filtering mode; detect that the instantaneous value of the AC voltage is greater than or equal to the given voltage value corresponding to the bus voltage, control the step-up circuit to work in the rectification mode, and control all The step-down circuit works in a step-down mode.
  • the step-up circuit is controlled to work in the rectification mode, and the step-down circuit is controlled to work in the filtering mode, and there is still no need
  • the step-up or step-down process does not need to control the power tube, the first power tube and the second power tube to perform modulation work, which is beneficial to reduce the power consumption of the drive circuit.
  • the step-up circuit is controlled to operate in the rectification mode, and the step-down circuit is controlled to operate in the step-down mode.
  • the boost circuit works in diode rectification or synchronous rectification state
  • the buck circuit works in pass-through filtering state.
  • the step-down circuit is controlled to operate in a filter mode or a step-down mode, and the step-up is controlled
  • the type circuit works in power factor correction mode or rectification mode, which specifically includes: determining the product of the effective value of the AC voltage and the first voltage coefficient, and recording the product as the first voltage sampling value; determining the value of the AC voltage The product between the effective value and the second voltage coefficient, and the product is recorded as the second voltage sample value; it is detected that the first voltage sample value is less than the given voltage value corresponding to the bus voltage, and the first voltage sample value is detected 2.
  • the voltage sampling value is greater than or equal to the given voltage value corresponding to the bus voltage, and the instantaneous value of the AC voltage is detected; if the instantaneous value of the AC voltage is detected to be less than the given voltage value corresponding to the bus voltage, the control station
  • the step-up circuit works in a power factor correction mode, and the step-down circuit is controlled to work in a filter mode; it is detected that the instantaneous value of the AC voltage is greater than or equal to the given voltage value corresponding to the bus voltage, and the The step-up circuit operates in the rectification mode, and the step-down circuit is controlled to operate in the step-down mode.
  • the first voltage sampling value is less than the second voltage sampling value, if it is detected that the first voltage sampling value is less than the given voltage value corresponding to the bus voltage, and the second voltage sampling value is detected If it is greater than or equal to the given voltage value corresponding to the bus voltage, then continue to predict and detect the rising trend of the AC voltage, and therefore continue to detect the instantaneous value of the AC voltage.
  • the step-up circuit is controlled to work in the power factor correction mode to improve the power supply efficiency.
  • the step-down circuit works in a filtering mode to further filter the noise in the power supply signal to improve the reliability of load operation.
  • the step-down circuit is controlled to operate in a filtering mode or a step-down mode
  • the step-up circuit is controlled to operate in a power factor correction mode or a rectification mode , Specifically including: determining the product between the effective value of the AC voltage and the second voltage coefficient, and recording the product as the second voltage sampling value; detecting that the second voltage sampling value is less than the voltage corresponding to the bus voltage Given a given value, the step-up circuit is controlled to work in a power factor correction mode.
  • the step-up circuit is controlled to work in the boost mode, that is, the DC bus is reduced by boosting in time.
  • the buck circuit in the boost mode, is in a filtering state, and at the same time, the boost circuit works in a boost modulation state.
  • the motor is a permanent magnet synchronous motor
  • the driving method further includes: determining the rotation speed and back electromotive force coefficient of the permanent magnet synchronous motor; The back electromotive force coefficient determines the given voltage value corresponding to the bus voltage.
  • the given voltage value corresponding to the bus voltage is determined by the back electromotive force coefficient, which is beneficial to further improve the reliability and flexibility of the buck-boost adjustment of the DC bus voltage.
  • the BUCK circuit when the boost circuit works in diode rectification and synchronous rectification states, the BUCK circuit can work either in the pass-through filtering state or in the BUCK step-down control state; when the boost circuit works In the boost PFC control state, the BUCK circuit can only work in the pass-through filtering state.
  • the working state of the boost circuit includes diode rectification, synchronous rectification and boost PFC control.
  • the diode rectification state that is, the four power switch tubes are all in the off state, and their anti-parallel diodes are used for rectification.
  • Synchronous rectification state that is, the four power switch tubes are all in the low-frequency switching state.
  • the current power switch tube For one of the bridge arms (such as T1 and T3), when the anti-parallel diode of the power switch tube has current flowing, the current power switch tube is turned on; On the other side of the bridge arm (such as T2 and T4), when the anti-parallel diode of the power switch tube has current flowing, the current power switch tube is turned on, or when the anti-parallel diode of the power switch tube has current flowing in the half cycle Turn on the current power switch and turn off in the other half of the cycle.
  • Boost PFC control state one side of the bridge arm (such as T1 and T2) is controlled by high-frequency switching to realize the boost adjustment function, according to the set value and detection value of the DC bus voltage, and the detection of AC input voltage and AC input current Closed-loop control of the sixth power tube T4 on the other side of the bridge arm is low-frequency switching control to achieve synchronous rectification, that is, when the anti-parallel diode of the power switching tube has current flowing, the current power switching tube is turned on, or when the power switching tube In the anti-parallel diode of the current flow, the current power switch tube is turned on in the half cycle, and the other half cycle time is turned off, and the fifth power tube T3 on the other side of the bridge arm is turned off.
  • the high-frequency switch of one side of the bridge arm (such as T3 and T4) to realize the boost adjustment function, according to the set value and detection value of the DC bus voltage, and the detection of AC input voltage and AC input current Detect closed-loop control.
  • the fourth power tube T2 on the other side of the bridge arm is controlled by the low-frequency switch and realizes the synchronous rectification function.
  • the current power switch tube is turned on in the half cycle when the current flows through the parallel diode, and the third power tube T1 on the other side of the bridge arm is turned off in the other half cycle time.
  • semi-synchronous rectification 1 that is, for one side of the bridge arms (such as T1 and T3) are in the off state, the anti-parallel diode is used for rectification; for the other side of the bridge arm (Such as T2 and T4), when the anti-parallel diode of the power switch tube has current flowing, the current power switch tube is turned on, or when the anti-parallel diode of the power switch tube has current flowing through the half cycle, the current power switch tube is turned on , The other half of the cycle time is off.
  • semi-synchronous rectification two that is, for one of the bridge arms (such as T1 and T3), when the anti-parallel diode of the power switch tube has current flowing, the current power switch tube is turned on , Or, when the anti-parallel diode of the power switch tube is turned on in the half cycle when the current flows, and the other half cycle time is turned off; for the other side of the bridge arm (such as T2 and T4) are in the off state , Use its anti-parallel diode for rectification.
  • the working state of the BUCK circuit includes through filtering and BUCK step-down control.
  • the third power tube T1 is controlled to be continuously turned on and the fourth power tube T2 is continuously turned off, so that the current is passed through and passed through the LC filter.
  • the BUCK step-down control state by controlling the third power tube T1, the step-down adjustment function is realized, and closed-loop control is performed according to the set value and detection value of the DC bus voltage.
  • the fourth power tube T2 is controlled to be turned off.
  • the fourth power tube T2 is controlled to be turned on or turned off.
  • the boost circuit works in the diode rectification state or the synchronous rectification state (second-selected semi-synchronous rectification), and the BUCK circuit works in the pass-through filtering state (equivalent to the ⁇ filter ).
  • the step-up circuit works in the diode rectification state or the synchronous rectification state (second-selected semi-synchronous rectification), and the BUCK circuit works in the BUCK step-down control state.
  • the boost circuit works in the boost PFC control state
  • the BUCK circuit works in the pass-through filtering state (equivalent to the ⁇ filter).
  • determine the working mode switching in a cycle which specifically includes the following methods:
  • the given DC bus voltage is less than or equal to the effective value of the AC voltage ⁇ the first voltage coefficient: the absolute value of the instantaneous AC voltage is less than the given DC bus voltage and enters the voltage non-control mode, otherwise it enters the step-down control mode.
  • the boost control mode will be entered, otherwise it will enter the step-down Control mode.
  • the first voltage coefficient is less than or equal to 1.4
  • the second voltage coefficient is greater than or equal to 1.0
  • the first voltage coefficient is less than or equal to the second voltage coefficient.
  • the DC bus voltage setting is determined according to the permanent magnet synchronous motor speed and its phase voltage back EMF coefficient.
  • the DC bus voltage setting speed ⁇ phase voltage back EMF coefficient ⁇ first Three voltage coefficients.
  • step S302 determining the AC voltage input to the driving circuit and the bus of the driving circuit Voltage
  • step S304 according to the AC voltage and the bus voltage, control the step-down circuit to work in a filter mode or a step-down mode, and control the totem pole circuit to work in a power factor correction mode or a rectification mode.
  • a totem pole circuit and a step-down circuit are provided in the drive circuit, and the totem pole circuit is controlled to work in rectification mode or power factor correction mode according to the AC voltage and the bus voltage, and control
  • the step-down circuit works in a step-down mode or a filtering mode, and realizes the step-up and step-down adjustment of the bus voltage, which can make the bus voltage higher than the peak value of the AC voltage or lower the bus voltage than the peak value of the AC voltage to improve the motor Efficiency and reliability, especially for permanent magnet synchronous motors, can reduce the iron loss of the motor by reducing the bus voltage.
  • the power supply signal generally refers to the signal that flows through the drive circuit and drives the load.
  • the input signal of the bridge circuit is an AC signal
  • the output is a bus DC signal. Therefore, the AC current and AC voltage are collected at the input end of the bridge circuit, and the DC current and DC bus voltage are collected at the output end of the bridge circuit.
  • a plurality of semiconductor switches are provided in the totem pole circuit and the step-down circuit.
  • the semiconductor switches are controlled by a controller.
  • a signal modulates the working state of the semiconductor switch, and then adjusts the working state of the totem pole circuit and/or the step-down circuit.
  • the step-down circuit is controlled to operate in a filter mode or a step-down mode
  • the totem pole circuit is controlled to be in a power factor correction mode Or rectification mode operation, specifically including: determining the given voltage value corresponding to the bus voltage; comparing the magnitude relationship between the given voltage value and the AC voltage; according to the relationship between the given voltage value and the AC voltage Control the step-down circuit to work in the filtering mode or the step-down mode, and control the totem pole circuit to work in the power factor correction mode or the rectification mode.
  • the step-down circuit is controlled to operate in the filtering mode or the step-down mode, and the totem pole circuit is controlled to Power factor correction mode or rectification mode operation, in order to improve the working efficiency of the drive circuit, when the step-down circuit works in the step-down mode, the totem pole circuit works in the rectification mode, or when the totem pole circuit works in the power factor correction mode, the The step-down circuit works in a filter mode. In addition, the step-down circuit works in a filter mode. At the same time, the totem pole circuit can work in a rectification mode.
  • the step-down circuit is controlled to operate in a filter mode or a step-down mode, and the totem pole circuit is controlled to be in a power factor correction mode Or rectification mode operation, which specifically includes: determining the product of the effective value of the AC voltage and the first voltage coefficient, and recording the product as the first voltage sampling value; detecting that the first voltage sampling value is greater than or equal to the bus Voltage corresponding to the given voltage value, detect the instantaneous value of the AC voltage; detect that the instantaneous value of the AC voltage is less than the given voltage value corresponding to the bus voltage, control the totem pole circuit to work in rectification mode, and control
  • the step-down circuit works in a filtering mode; it is detected that the instantaneous value of the AC voltage is greater than or equal to the given voltage value corresponding to the bus voltage, the totem pole circuit is controlled to work in the rectification mode, and the step-down is controlled
  • the type circuit works in step-down mode
  • the totem pole circuit is controlled to work in the rectification mode, and the step-down circuit is controlled to work in the filtering mode.
  • the step-up or step-down processing does not need to control the power tube, the first power tube and the second power tube for modulation work, which is beneficial to reduce the power consumption of the drive circuit.
  • the totem pole circuit works in the diode rectification or synchronous rectification state
  • the step-down circuit works in the pass-through filtering state.
  • the step-down circuit is controlled to work in a filter mode or a step-down mode, and the totem pole is controlled
  • the circuit works in power factor correction mode or rectification mode, which specifically includes: determining the product of the effective value of the AC voltage and the first voltage coefficient, and recording the product as the first voltage sampling value; determining the effective value of the AC voltage The product between the value and the second voltage coefficient, and the product is recorded as the second voltage sample value; it is detected that the first voltage sample value is less than the given voltage value corresponding to the bus voltage, and the second voltage value is detected If the voltage sampling value is greater than or equal to the given voltage value corresponding to the bus voltage, the instantaneous value of the AC voltage is detected; it is detected that the instantaneous value of the AC voltage is less than the given voltage value corresponding to the bus voltage, and the The totem pole circuit operates in a power factor correction mode, and controls the step-down circuit to operate in a
  • the first voltage sampling value is less than the second voltage sampling value, if it is detected that the first voltage sampling value is less than the given voltage value corresponding to the bus voltage, and the second voltage sampling value is detected If it is greater than or equal to the given voltage value corresponding to the bus voltage, then continue to predict and detect the rising trend of the AC voltage, and therefore continue to detect the instantaneous value of the AC voltage.
  • the totem pole circuit is controlled to work in the power factor correction mode to improve the power supply efficiency.
  • the profiling circuit works in a filtering mode to further filter the noise in the power supply signal to improve the reliability of load operation.
  • controlling the step-down circuit to operate in a filter mode or a step-down mode, and controlling the totem pole circuit to operate in a power factor correction mode or a rectification mode includes: determining the product between the effective value of the AC voltage and the second voltage coefficient, and recording the product as the second voltage sampling value; detecting that the second voltage sampling value is less than the voltage corresponding to the bus voltage Set the value to control the totem pole circuit to work in the power factor correction mode.
  • the totem pole circuit is controlled to work in a boost mode, that is, the DC bus voltage is reduced by boosting in time The possibility of falling and stopping of the motor.
  • the buck circuit in the boost mode, is in a filtering state, and at the same time, the totem pole circuit works in a boost modulation state.
  • the motor is a permanent magnet synchronous motor
  • the driving method further includes: determining the rotation speed and back electromotive force coefficient of the permanent magnet synchronous motor; The back electromotive force coefficient determines the given voltage value corresponding to the bus voltage.
  • the given voltage value corresponding to the bus voltage is determined by the back electromotive force coefficient, which is beneficial to further improve the reliability and flexibility of the buck-boost adjustment of the DC bus voltage.
  • the BUCK circuit when the totem pole circuit works in the diode rectification and synchronous rectification state, the BUCK circuit can work either in the pass-through filtering state or in the BUCK step-down control state; when the totem pole circuit is working in the rising state When the PFC control state is pressed, the BUCK circuit can only work in the pass-through filtering state.
  • the working state of the totem pole circuit includes diode rectification, synchronous rectification and boost PFC control.
  • Diode rectification state that is, the four power switches are all in the off state, and their anti-parallel diodes are used for rectification.
  • Synchronous rectification state that is, the four power switch tubes are all in the low-frequency switching state.
  • the current power switch tube is turned on when the anti-parallel diode of the power switch tube has current flowing;
  • the current power switch tube is turned on, or when the anti-parallel diode of the power switch tube has current flowing in the half cycle Turn on the current power switch and turn off in the other half of the cycle.
  • Boost PFC control state one side of the bridge arm (such as T1 and T2) is controlled by high-frequency switching to realize the boost adjustment function, according to the set value and detection value of the DC bus voltage, and the detection of AC input voltage and AC input current Closed-loop control; the other side of the bridge arm (such as T3 and T4) is controlled by low-frequency switching to realize the synchronous rectification function, that is, when the anti-parallel diode of the power switch tube has current flowing, the current power switch tube is turned on, or when the power switch The anti-parallel diode of the tube turns on the current power switch tube in the half cycle when the current flows, and turns off in the other half cycle.
  • semi-synchronous rectification 1 that is, for one side of the bridge arms (such as T1 and T2) are in the off state, the anti-parallel diode is used for rectification; for the other side of the bridge arm (For example, T3 and T4), the current power switch is turned on when the anti-parallel diode of the power switch has current flowing, or when the current is flowing through the anti-parallel diode of the power switch, the current power switch is turned on , The other half of the cycle time is off.
  • semi-synchronous rectification two that is, for one of the bridge arms (such as T1 and T2), when the anti-parallel diode of the power switch tube has current flowing, the current power switch tube is turned on , Or, when the anti-parallel diode of the power switch tube is turned on in the half cycle when the current flows, the current power switch tube is turned off in the other half cycle; for the other side of the bridge arm (such as T3 and T4) are in the off state , Use its anti-parallel diode for rectification.
  • the working state of the BUCK circuit includes through filtering and BUCK step-down control.
  • the through filtering state controls the first power tube Q1 to be continuously turned on and the second power tube Q2 to continuously turn off to achieve current flow through and LC filtering.
  • the step-down regulation function is realized by controlling the first power tube Q1, and the closed-loop control is performed according to the set value and the detected value of the DC bus voltage.
  • the first power tube Q1 is turned on, the second power tube Q2 is controlled to turn off; when the first power tube Q1 is turned off, the second power tube Q2 is controlled to turn on or off.
  • the totem pole circuit works in the diode rectification state or the synchronous rectification state (second-selected semi-synchronous rectification), and the BUCK circuit works in the pass-through filtering state (equivalent to the ⁇ filter) .
  • the totem pole circuit works in the diode rectification state or the synchronous rectification state (second-selected semi-synchronous rectification), and the BUCK circuit works in the BUCK step-down control state;
  • the totem pole circuit works in the boost PFC control state
  • the BUCK circuit works in the pass-through filtering state (equivalent to the ⁇ filter).
  • determine the working mode switching in a cycle which specifically includes the following methods:
  • the given DC bus voltage is less than or equal to the effective value of the AC voltage ⁇ the first voltage coefficient: the absolute value of the instantaneous AC voltage is less than the given DC bus voltage and enters the voltage non-control mode, otherwise it enters the step-down control mode.
  • the boost control mode will be entered, otherwise it will enter the step-down Control mode.
  • the first voltage coefficient is less than or equal to 1.4
  • the second voltage coefficient is greater than or equal to 1.0
  • the first voltage coefficient is less than or equal to the second voltage coefficient.
  • the DC bus voltage setting is determined according to the permanent magnet synchronous motor speed and its phase voltage back EMF coefficient.
  • the DC bus voltage setting speed ⁇ phase voltage back EMF coefficient ⁇ first Three voltage coefficients.
  • 1 ⁇ third voltage coefficient ⁇ 2.5; preferably, 1.5 ⁇ third voltage coefficient ⁇ 2.
  • Embodiment 6 is a diagrammatic representation of Embodiment 6
  • step S302 determining the AC voltage input to the driving circuit and the bus of the driving circuit Voltage
  • step S304 according to the AC voltage and the bus voltage, control the step-down circuit 100 to operate in a rectification mode or a step-down mode, and control the step-up circuit 200 to operate in a step-up mode or a filter mode .
  • a step-down circuit 100 and a step-up circuit 200 are provided in the drive circuit.
  • the step-down circuit 100 is controlled to operate in a rectification mode or a step-down mode.
  • the boost circuit 200 to work in boost mode or filter mode to realize the step-up and step-down regulation of the bus voltage, as shown in Figure 29 and Figure 30, which can make the bus voltage higher than the peak value of the AC voltage .
  • the bus voltage can also be lower than the peak value of the AC voltage to improve the efficiency and reliability of the motor.
  • the iron loss of the motor can be reduced by reducing the bus voltage.
  • the power supply signal generally refers to a signal that flows through the driving circuit and drives the load M to operate.
  • the input signal of the bridge circuit is an AC signal AC
  • the output is a bus DC signal. Therefore, the AC current and AC voltage are collected at the input end of the bridge circuit, and the DC current and DC bus voltage are collected at the output end of the bridge circuit.
  • the step-down circuit 100 and the step-up circuit 200 are provided with a plurality of semiconductor switches, the semiconductor switches are controlled by a controller, and the controller is based on the collected AC voltage, AC current, DC bus voltage and DC bus current. At least one signal in modulates the working state of the semiconductor switch, thereby adjusting the working state of the buck circuit 100 and/or the boost circuit 200.
  • the BOOST circuit can work in the pass-through filtering state or the BOOST boost control state; when the bridgeless BUCK circuit works in the BUCK step-down control state When, the BOOST circuit can only work in the pass-through filtering state.
  • the working state of the bridgeless BUCK circuit includes diode rectification, synchronous rectification, diode rectification + BUCK step-down control (as shown in Figure 57), and synchronous rectification + BUCK step-down control (as shown in Figure 20).
  • the eighth power tube T12 and the ninth power tube T14 are both in the off state, and their anti-parallel diodes are used for rectification.
  • the first unidirectional conducting tube T11 is at the drain voltage of the first unidirectional conducting tube T11 When the voltage is higher than the source voltage, it turns on, and vice versa, the second one-way conductive transistor T13 turns on when the drain voltage of the second one-way transistor T13 is higher than the source voltage, and vice versa.
  • the first one-way conduction transistor T11 turns on when the drain voltage of the first one-way conduction transistor T11 is higher than the source voltage, and vice versa
  • the second one-way conduction transistor T13 turns on in the second one-way conduction transistor T13.
  • the eighth power transistor T12 is turned on when the drain voltage of the second unidirectional conduction transistor T13 is higher than the source voltage, and vice versa
  • the ninth power transistor T14 When the drain voltage of the first unidirectional conducting transistor T11 is higher than the source voltage, it is turned on, and vice versa.
  • Diode rectification + BUCK step-down control state the first one-way conduction transistor T11 performs PWM duty cycle adjustment control when the drain voltage of the first one-way conduction transistor T11 is higher than the source voltage, and the second one-way conduction transistor T13 adjusts and controls the PWM duty cycle when the drain voltage of the second unidirectional conduction transistor T13 is higher than the source voltage; the eighth power transistor T12 and the ninth power transistor T14 are both in the off state.
  • the first one-way conduction transistor T11 performs PWM duty cycle adjustment control when the drain voltage of the first one-way conduction transistor T11 is higher than the source voltage, and the second one-way conduction transistor T13 PWM duty cycle adjustment control when the drain voltage of the second one-way conduction transistor T13 is higher than the source voltage;
  • the eighth power transistor T12 turns on when the drain voltage of the second one-way conduction transistor T13 is higher than the source voltage, and vice versa Turn off;
  • the ninth power transistor T14 turns on when the drain voltage of the first unidirectional conducting transistor T11 is higher than the source voltage, and vice versa.
  • FIG. 59 a schematic diagram of the switching state of the power switching device under two modes of (diode rectification + BUCK step-down + LC filtering) and (diode rectification + BOOST boost).
  • FIG. 60 a schematic diagram of the switching state of the power switching device under two modes of (synchronous rectification + BUCK step-down + LC filtering) and (synchronous rectification + BOOST boost).
  • the working state of the BOOST circuit includes through filtering and BUCK step-down control, as follows:
  • (2) BOOST boost control state by controlling the power switch tube, the tenth power tube Q13, the boost regulation function is realized, and the closed-loop control is carried out according to the set value and detection value of the DC bus voltage.
  • the eleventh power tube Q13 of the power switch tube is turned on, the eleventh power tube Q12 of the power switch tube is controlled to turn off; when the tenth power tube Q13 of the power switch tube is turned off, the eleventh power tube Q12 of the power switch tube is controlled to turn on. On or off.
  • the uncontrolled modes of the drive circuit include the following:
  • the bridgeless BUCK circuit works in the diode rectification state (as shown in Figure 55) or the synchronous rectification state (as shown in Figure 56), and the BOOST circuit works in the pass-through filtering state, which is equivalent to an LC filter. .
  • the bridgeless BUCK circuit works in the diode rectification + BUCK step-down control state or the synchronous rectification + BUCK step-down control state
  • the BOOST circuit works in the pass-through filtering state, which is equivalent to an LC filter.
  • the bridgeless BUCK circuit works in the boost diode rectification state or the synchronous rectification state
  • the BOOST circuit works in the BOOST boost control state.
  • the step-down circuit 100 is controlled to operate in a rectification mode or a step-down mode
  • the step-up circuit 200 is controlled to increase Working in voltage mode or filtering mode, specifically including: determining a given voltage value corresponding to the bus voltage; comparing the magnitude relationship between the given voltage value and the AC voltage; and according to the given voltage value and the AC voltage
  • the magnitude of the relationship between the step-down circuit 100 is controlled to operate in the rectification mode or the step-down mode
  • the step-up circuit 200 is controlled to operate in the step-up mode or the filter mode.
  • the step-down circuit 100 is controlled to operate in the rectification mode or the step-down mode, and the step-up mode is controlled.
  • the circuit 200 works in a boost mode or a filter mode.
  • the boost circuit 200 works in the filter mode, or the boost circuit 200 works in the boost mode.
  • the buck circuit 100 works in a rectifier mode.
  • the buck circuit 100 works in a rectifier mode.
  • the boost circuit can work in a filter mode.
  • the step-down circuit 100 is controlled to operate in a rectification mode or a step-down mode
  • the step-up circuit 200 is controlled to increase Working in voltage mode or filtering mode, specifically including: determining the product between the effective value of the AC voltage and the first voltage coefficient, and recording the product as the first voltage sample value; detecting that the first voltage sample value is greater than or Equal to the given voltage value corresponding to the bus voltage, control the step-down circuit 100 to work in the step-down mode, and control the step-up circuit 200 to work in the filtering mode; detect the first voltage sample If the value is less than the given voltage value corresponding to the bus voltage, the step-down circuit 100 is controlled to work in the rectification mode, and the step-up circuit 200 is controlled to work in the filtering mode.
  • the instantaneous value of the AC voltage can be determined, and the absolute value of the instantaneous AC voltage
  • the uncontrolled mode Entering the uncontrolled mode at this time will help reduce the power consumption of the drive circuit. Otherwise, it will enter the step-down control mode to reduce the AC voltage in time, and then reduce The impact of AC voltage on the subsequent circuit of the step-down circuit 100.
  • the buck circuit 100 works in a diode rectification or synchronous rectification state
  • the boost circuit 200 works in a through filtering state.
  • the step-down circuit 100 is controlled to operate in a rectification mode or a step-down mode
  • the step-up circuit 200 is controlled to increase Voltage mode or filtering mode, specifically including: determining the product of the effective value of the AC voltage and the first voltage coefficient, and recording the product as the first voltage sampling value; determining the effective value of the AC voltage and the second The product between the voltage coefficients, and the product is recorded as the second voltage sample value; it is detected that the first voltage sample value is less than the given voltage value corresponding to the bus voltage, and it is detected that the second voltage sample value is greater than Or equal to the given voltage value corresponding to the bus voltage, detecting the instantaneous value of the AC voltage; detecting that the instantaneous value of the AC voltage is less than the given voltage value corresponding to the bus voltage, and controlling the boost circuit 200 works in the boost mode, and controls the buck circuit 100 to work in the rectification mode; detects that the instantaneous value
  • the first voltage sampling value is less than the second voltage sampling value, if it is detected that the first voltage sampling value is less than the given voltage value corresponding to the bus voltage, and the second voltage sampling value is detected If it is greater than or equal to the given voltage value corresponding to the bus voltage, then continue to predict and detect the rising trend of the AC voltage, and therefore continue to detect the instantaneous value of the AC voltage.
  • the step-down circuit 100 is controlled to work in the step-down mode to reduce the AC voltage in a timely manner.
  • the boost circuit 200 works in the filtering mode to improve the efficiency of the driving circuit.
  • the step-down circuit 100 is controlled to operate in a rectification mode or a step-down mode
  • the step-up circuit 200 is controlled to increase Voltage mode or filtering mode, specifically including: determining the product of the effective value of the AC voltage and the second voltage coefficient, and recording the product as the second voltage sampling value; detecting that the second voltage sampling value is less than the The voltage given value corresponding to the bus voltage controls the step-up circuit 200 to work in a step-up mode.
  • the step-up circuit 200 is controlled to operate in the step-up mode, that is, to reduce the direct current by stepping up in time.
  • the buck circuit 100 works in a rectification state, and at the same time, the boost circuit 200 works in a boost modulation state.
  • the motor is a permanent magnet synchronous motor
  • the driving method further includes: determining the rotation speed and back electromotive force coefficient of the permanent magnet synchronous motor; The back electromotive force coefficient determines the given voltage value corresponding to the bus voltage.
  • the given voltage value corresponding to the bus voltage is determined by the back electromotive force coefficient, which is beneficial to further improve the reliability and flexibility of the buck-boost adjustment of the DC bus voltage.
  • the DC bus voltage setting rotation speed ⁇ phase voltage back-EMF coefficient ⁇ third voltage coefficient.
  • 1 ⁇ third voltage coefficient ⁇ 2.5.
  • the rectification mode includes a diode rectification mode and a synchronous rectification mode.
  • an air conditioner 400 including: a motor 402; a buck-boost driving circuit 404 defined by any of the above technical solutions, and the driving circuit 404 is configured To control the operation of the motor 402.
  • the air conditioner includes the buck-boost driving circuit as in any of the above technical solutions. Therefore, the air conditioner includes all the beneficial effects of the buck-boost driving circuit as in any of the above technical solutions. Go into details.
  • a computer-readable storage medium 500 is provided, the computer-readable storage medium 500 stores a computer program, and the computer program is executed by an air conditioner 400 When realizing the driving method defined by any one of the above technical solutions.
  • the term “plurality” refers to two or more than two, unless specifically defined otherwise.
  • the directions or positional relationships indicated by the terms “upper” and “lower” are those based on the drawings, which are only for the convenience of describing the application and simplifying the description, and do not indicate or imply that the device or element referred to must have a specific Therefore, it cannot be construed as a limitation of this application.
  • the terms “installed”, “connected”, “connected”, “fixed”, etc. should be understood in a broad sense. For example, “connected” can be a fixed connection, a detachable connection, or an integral connection; “connected” can be Directly connected, or indirectly connected through an intermediary.
  • the specific meanings of the above-mentioned terms in this application can be understood according to specific circumstances.

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Abstract

一种升降压驱动电路、方法、空调器和计算机可读存储介质，其中，升降压驱动电路包括：升压型电路，被配置为能够对供电信号进行功率因数校正处理或整流处理；降压型电路，输入端连接至升压型电路的输出端；降压型电路包括：第一功率管（Q1）和第二功率管（Q2），依次串联于升压型电路的高压输出端和低压输出端之间，第二功率管（Q2）的两端引出为高压母线和低压母线；控制第一功率管（Q1）和第二功率管（Q2）交替导通，以对所述高压母线和所述低压母线之间的母线电压进行降压调制。该升降压驱动电路有利于降低电机的铁损，以提高变频电机的效率。

Description

升降压驱动电路、方法、空调器和计算机可读存储介质
本申请要求于2020年03月17日提交中国国家知识产权局、申请号为202010188759.2、发明名称为“升降压驱动电路、方法、空调器和计算机可读存储介质”的中国专利申请、于2020年03月17日提交中国国家知识产权局、申请号为202010188159.6、发明名称为“升降压驱动电路、方法、空调器和计算机可读存储介质”的中国专利申请、于2020年03月17日提交中国国家知识产权局、申请号为202020341297.9、发明名称为“升降压驱动电路和空调器”的中国专利申请、以及于2020年03月17日提交中国国家知识产权局、申请号为202010188837.9、发明名称为“升降压驱动电路、方法、空调器和计算机可读存储介质”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请涉及电机技术领域，具体而言，涉及一种升降压驱动电路、一种升降压驱动方法、一种空调器和一种计算机可读存储介质。
背景技术
一般而言，变频空调的高效变频压缩机的驱动电机通常是永磁电机，因此，电机的铁损主要受到变频控制器的直流母线电压的影响。
譬如，在不进入弱磁运行的情况下，直流母线电压越高，电机铁损越大，直流母线电压越低，电机铁损越小。因此，可以适当调低直流电压，以减小电机铁损，以及提高电机效率。
相关技术中，变频空调的功率因数校正(Power Factor Correction,PFC)都没有降压功能。例如，无源PFC、单脉冲和多脉冲PFC均没有调节直流母线电压功能，而典型的boost PFC只能进行升压调节，而不能进行降压调节。
另外，整个说明书对背景技术的任何讨论，并不代表该背景技术一定是所属领域技术人员所知晓的现有技术，整个说明书中的对现有技术的任何讨论并不代表认为该现有技术一定是广泛公知的或一定构成本领域的公知常识。
发明内容
本申请旨在至少解决现有技术或相关技术中存在的技术问题之一。
为此，本申请的第一方面提供一种升降压驱动电路。
本申请的第二方面提供另一种升降压驱动电路。
本申请的第三方面提供再一种升降压驱动电路。
本申请的第四方面提供一种升降压驱动方法。
本申请的第五方面提供另一种升降压驱动方法。
本申请的第六方面提供再一种升降压驱动方法。
本申请的第七方面提供一种空调器。
本申请的第八方面提供一种计算机可读存储介质。
有鉴于此，本申请的第一方面提供了一种升降压驱动电路，包括：升压型电路，所述升压型电路被配置为能够对供电信号进行功率因数校正处理或整流处理；降压型电路，所述降压型电路的输入端连接至所述升压型电路的输出端，所述降压型电路包括：第一功率管和第二功率管，依次串联于所述升压型电路的高压输出端和低 压输出端之间，所述第二功率管的两端引出为高压母线和低压母线，其中，控制所述第一功率管和第二功率管交替导通，以对所述高压母线和所述低压母线之间的母线电压进行降压调制。
在该技术方案中，通过在驱动电路中设置升压型电路和降压型电路，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
具体地，升压型电路和降压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整升压型电路和/或降压型电路的工作状态。
另外，升压型电路可以是图腾柱电路，也可以是整流器和PFC电路的组合。
本申请的第二方面提供了另一种升降压驱动电路，包括：图腾柱电路，所述图腾柱电路被配置为能够对供电信号进行功率因数校正处理或整流处理；降压型电路，所述降压型电路的输入端连接至所述图腾柱电路的输出端，所述降压型电路包括：第一功率管和第二功率管，依次串联于所述图腾柱电路的高压输出端和低压输出端之间，所述第二功率管的两端引出为高压母线和低压母线，其中，控制所述第一功率管和第二功率管交替导通，所述高压母线和低压母线之间的母线电压随着负载运行时长增大而降低，所述降压型电路被配置为能够对所述供电信号进行降压处理或滤波处理。
在该技术方案中，通过在驱动电路中设置图腾柱电路和降压型电路，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
具体地，图腾柱电路和降压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整图腾柱电路和/或降压型电路的工作状态。
本申请的第三方面提供了再一种升降压驱动电路，包括：降压型电路，所述降压型电路包括：桥式电路，所述桥式电路的任一桥臂中设有一个半导体管，所述降压型电路被配置为接入供电端输入的供电信号；所述升压型电路，所述升压型电路的输入端连接至所述降压型电路的输出端，所述升压型电路被配置为能够升高所述供电信号；第七功率管，连接至所述桥式电路的两个输出端，且连接至所述升压型电路的两个输入端，所述第七功率管被配置为能够对所述升压型电路进行续流。
在该技术方案中，通过在驱动电路中设置降压型电路和升压型电路，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
具体地，降压型电路和升压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整降压型电路和/或升压型电路的工作状态。
本申请的第四方面提供了一种升降压驱动方法，包括：确定输入至所述驱动电 路的交流电压，以及所述驱动电路的母线电压；根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作。
在该技术方案中，在驱动电路中设置升压型电路和降压型电路，根据所述交流电压和所述母线电压，通过控制所述升压型电路以功率因数校正模式或整流模式工作，以及控制所述降压型电路以滤波模式或降压模式工作，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
具体地，升压型电路和降压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整升压型电路和/或降压型电路的工作状态。
本申请的第五方面提供了另一种升降压驱动方法，包括：确定输入至所述驱动电路的交流电压，以及所述驱动电路的母线电压；根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作。
在该技术方案中，在驱动电路中设置图腾柱电路和降压型电路，根据所述交流电压和所述母线电压，通过控制所述图腾柱电路以功率因数校正模式或整流模式工作，以及控制所述降压型电路以滤波模式或降压模式工作，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
具体地，图腾柱电路和降压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整图腾柱电路和/或降压型电路的工作状态。
本申请的第六方面提供了再一种升降压驱动方法，包括：确定输入至所述驱动电路的交流电压，以及所述驱动电路的母线电压；根据所述交流电压和所述母线电压，控制所述降压型电路以整流模式或降压模式工作，以及控制所述升压型电路以升压模式或滤波模式工作。
在该技术方案中，在驱动电路中设置降压型电路和升压型电路，根据所述交流电压和所述母线电压，通过控制所述降压型电路以整流模式或降压模式工作，以及控制所述升压型电路以升压模式或滤波模式工作，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
具体地，降压型电路和升压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整降压型电路和/或升压型电路的工作状态。
其中，在上述任一技术方案中，供电信号泛指流经驱动电路并驱动负载运行的信号，桥式电路的输入信号为交流信号，输出为母线直流信号。因此，在桥式电路 的输入端采集交流电流和交流电压，在桥式电路的输出端采集直流电流和直流母线电压。
本申请的第七方面提供了一种空调器，包括：电机；如上述任一技术方案限定的升降压驱动电路，升降压驱动电路被配置为控制电机运行。
在该技术方案中，空调器包括如上述任一技术方案中的升降压驱动电路，因此，该空调器包括如上述任一技术方案中的升降压驱动电路的全部有益效果，因此不再赘述。
本申请的第八方面提供了一种计算机可读存储介质，所述计算机可读存储介质上存储有计算机程序，所述计算机程序被执行时实现上述任一项技术方案限定的驱动方法。
附图说明
本申请的上述和/或附加的方面和优点从结合下面附图对实施例的描述中将变得明显和容易理解，其中：
图1示出了根据本申请的一个实施例的升降压驱动电路的结构图；
图2示出了根据本申请的另一个实施例的升降压驱动电路的结构图；
图3示出了根据本申请的再一个实施例的升降压驱动电路的结构图；
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图30示出了根据本申请的再一个实施例的升降压驱动方法的时序图；
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图44示出了根据本申请的一个实施例的升降压驱动方法的示意流程图；
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图60示出了根据本申请的又一个实施例的升降压驱动方法的时序图；
图61示出了根据本申请的又一个实施例的升降压驱动方法的时序图；
图62示出了根据本申请的又一个实施例的升降压驱动方法的时序图；
图63示出了根据本申请的再一个实施例的升降压驱动方法的示意流程图；
图64示出了根据本申请的一个实施例的空调器的示意框图；
图65示出了根据本申请的一个实施例的计算机可读存储介质的示意框图。
上述附图中的附图标记与结构之间的对应关系如下：
交流信号AC、第一功率管Q1、第二功率管Q2、第三功率管T1、第四功率管T2、第五功率管T3、第六功率管T4、第七功率管Q11、第一单向导通管T11、第八功率管T12、第二单向导通管T13、第九功率管T14、第十功率管Q13、第十一功率管Q12、降压型电路100、升压型电路200、负载M、逆变器IPM、第一感性元件L1、第二感性元件L2、第一容性元件C1、第二容性元件C2、第三感性元件L3、第三容性元件C3。
具体实施方式
为了能够更清楚地理解本申请的上述目的、特征和优点，下面结合附图和具体实施方式对本申请进行进一步的详细描述。需要说明的是，在不冲突的情况下，本申请的实施例及实施例中的特征可以相互组合。
在下面的描述中阐述了很多具体细节以便于充分理解本申请，但是，本申请还可以采用其他不同于在此描述的其他方式来实施，因此，本申请的保护范围并不限于下面公开的具体实施例的限制。
下面参照图1至图65描述根据本申请一些实施例的升降压驱动电路、方法、空调器和计算机可读存储介质。
实施例一：
如图1至图7所示，根据本申请第一方面的实施例，提供了一种升降压驱动电路，包括：升压型电路，所述升压型电路被配置为能够对供电信号进行功率因数校正处理或整流处理；降压型电路，所述降压型电路的输入端连接至所述升压型电路的输出端，所述降压型电路包括：第一功率管Q1和第二功率管Q2，依次串联于所述升压型电路的高压输出端和低压输出端之间，所述第二功率管Q2的两端引出为高压母线和低压母线，其中，控制所述第一功率管Q1和第二功率管Q2交替导通，以对所述高压母线和所述低压母线之间的母线电压进行降压调制。
在该技术方案中，通过在驱动电路中设置升压型电路和降压型电路，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对于永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
具体地，升压型电路和降压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整升压型电路和/或降压型电路的工作状态。
另外，升压型电路可以是图腾柱电路，也可以是整流器和PFC电路的组合。
其中，供电信号泛指流经驱动电路并驱动负载运行的信号，桥式电路的输入信号为交流信号AC，输出为母线直流信号。因此，在桥式电路的输入端采集交流电流和交流电压，在桥式电路的输出端采集直流电流和直流母线电压。
后文中，所述驱动控制电路的升压型电路也可被记作BOOST电路，降压型电路也可被记作BUCK电路。
如图2和图3所示，负载M可以是逆变器IPM及其驱动的永磁电机。
如图3所示，SVPWM的主要思想是以三相对称正弦波电压供电时三相对称电动机定子理想磁链圆为参考标准，以三相逆变器不同开关模式作适当的切换，从而形成PWM波，以所形成的实际磁链矢量来追踪其准确磁链圆。传统的SPWM方法从电源的角度出发，以生成一个可调频调压的正弦波电源，而SVPWM方法将逆变系统和异步电机看作一个整体来考虑，模型比较简单，也便于微处理器的实时控制。
另外，本申请提供的上述技术方案中的升降压驱动电路，还可以具有如下附加技术特征：
在上述技术方案中，进一步地，所述降压型电路包括：滤波电路，所述滤波电路与所述第二功率管Q2并联连接，所述滤波电路用于对流经所述高压母线和所述低压母线的供电信号进行滤波处理。
在该技术方案中，通过将降压型电路设置为包括滤波电路，滤波电路对母线直流信号进行滤波处理，在降压型电路的第一功率管Q1和第二功率管Q2进行调制工作时，实现对母线直流信号的降压处理，不仅有利于提升负载的运行效率，也有利于降低电机的铁损和噪声干扰。
在上述技术方案中，进一步地，所述滤波电路包括：第一感性元件L1，所述第一感性元件L1的第一端连接于所述第一功率管Q1和所述第二功率管Q2之间的公共端；第一容性元件C1，所述第一容性元件C1的第一端连接于所述第一感性元件L1的第二端，所述第一容性元件C1的第二端连接于所述低压母线。
在该技术方案中，通过将滤波电路设置为包括第一感性元件L1和第一容性元件C1，并按照上述方式连接，即在负载输入端接入LC滤波结构，滤除直流信号中携带的交流噪声，以进一步地提升负载运行的可靠性。
在上述技术方案中，进一步地，所述升压型电路包括：第二感性元件L2，所述第二感性元件L2被配置为接入所述供电信号；桥式电路，所述桥式电路的任一桥臂中设有一个功率管，所述桥式电路的输入端连接至所述第二感性元件L2，所述桥式电路被配置为能够对所述供电信号进行整流处理或功率因数校正处理；第二容性元件C2，所述第二容性元件C2连接于所述桥式电路的两个输出端之间。
在该技术方案中，通过设置第二感性元件L2、第二容性元件C2和桥式电路，并且按照上述方式进行连接，一方面，可以作为功率因数校正电路工作，另一方面，可以作为整流电路工作，不仅简化了电路结构，由于桥式电路的每个桥臂设置有功率管，有效地降低了电路功耗和延时。
在上述技术方案中，进一步地，所述桥式电路包括：第三功率管T1、第四功率管T2、第五功率管T3和第六功率管T4，所述第三功率管T1与所述第四功率管T2之间的公共端连接至所述第二感性元件L2的第一端，所述供电端的第一输出端与所述第二感性元件L2的第二端相连，所述第五功率管T3与所述第六功率管T4之间的公共端连接至所述供电端的第二输出端，其中，所述第三功率管T1和所述第五功率管T3的公共端作为所述高压输出端，所述第四功率管T2和所述第六功率管T4的公共端作为所述低压输出端。
在该技术方案中，通过将桥式电路设置为具体包括上述四个功率管，且以上述方式进行连接，可以对交流信号AC进行整流处理，另外，在桥式电路的功率管按照指定占空比进行调制升压时，输出的母线直流信号被升高。
如图5所示的等效电路可知，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以二极管整流模式工作，具体包括以下步骤：所述控制器控制所述桥式电路中的功率管均截止，所述反并联的第一二极管对所述供电信号进行整流。
在该技术方案中，所述控制器控制所述桥式电路中的功率管均截止，所述反并联的第一二极管对所述供电信号进行整流，桥式电路等效为二极管整流器，因此，实现对交流信号AC的整流处理。
在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以同步整流模式工作，具体包括以下步骤：所述反并联的第一二极管导通时，所述控制器控制对应的功率管以第一占空比导通。
在该技术方案中，在所述反并联的第一二极管导通时，通过所述控制器控制对 应的功率管以第一占空比导通，以实现同步整流处理，响应时间短且可靠性高。
在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以半同步整流模式工作，具体包括以下步骤：控制所述第三功率管T1和所述第五功率管T3截止，所述第四功率管T2的反并联的第一二极管导通时，所述控制器控制所述第四功率管T2导通，以及所述第六功率管T4的反并联的第一二极管导通时，所述控制器控制所述第六功率管T4导通。
在该技术方案中，通过控制所述第三功率管T1和所述第五功率管T3截止，即第三功率管T1的反并联的第一二极管导通，以及第五功率管T3的反并联的第一二极管导通。
另外，在所述第四功率管T2的反并联的第一二极管导通时，同时，所述控制器控制所述第四功率管T2导通，以及所述第六功率管T4的反并联的第一二极管导通时，所述控制器控制所述第六功率管T4导通，即采用第五功率管T3和第六功率管T4进行同步整流处理。
在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以半同步整流模式工作，具体包括以下步骤：控制所述第四功率管T2和所述第六功率管T4截止，所述第三功率管T1的反并联的第一二极管导通时，所述控制器控制所述第三功率管T1导通，以及所述第五功率管T3的反并联的第一二极管导通时，所述控制器控制所述第五功率管T3导通。
在该技术方案中，控制所述第四功率管T2和所述第六功率管T4截止，即第四功率管T2的反并联的第一二极管导通，以及第六功率管T4的反并联的第一二极管导通。
另外，所述第三功率管T1的反并联的第一二极管导通时，所述控制器控制所述第三功率管T1导通，以及所述第五功率管T3的反并联的第一二极管导通时，所述控制器控制所述第五功率管T3导通，即采用第三功率管T1和第五功率管T3进行同步整流处理。
如图6所示的等效电路可知，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以功率因数校正模式工作，具体包括以下步骤：所述供电信号向所述第三功率管T1和第四功率管T2之间的公共端流入时，所述第三功率管T1和所述第四功率管T2以第二占空比交替导通；所述第五功率管T3的反并联的第一二极管有电流流过时，所述控制器控制所述第五功率管T3以第三占空比导通，同时，所述控制器保持所述第六功率管T4截止；所述第六功率管T4的反并联的第一二极管有电流流过时，所述控制器控制所述第六功率管T4以第三占空比导通，同时，所述控制器保持所述第五功率管T3截止。
在该技术方案中，在所述供电信号向所述第三功率管T1和第四功率管T2之间的公共端流入时，通过控制所述第三功率管T1和所述第四功率管T2以第二占空比交替导通，且在所述第六功率管T4的反并联的第一二极管有电流流过时，所述控制器控制所述第六功率管T4以第三占空比导通，同时，所述控制器保持所述第五功率管T3截止，实现了对供电信号的功率因数校正处理。
同理，所述第五功率管T3的反并联的第一二极管有电流流过时，所述控制器控制所述第五功率管T3以第三占空比导通，同时，所述控制器保持所述第六功率 管T4截止，实现了对供电信号的功率因数校正处理。
如图6所示的等效电路可知，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以功率因数校正模式工作，具体包括以下步骤：所述供电信号向所述第五功率管T3和第六功率管T4之间的公共端流入时，所述第五功率管T3和所述第六功率管T4以第四占空比交替导通；所述第三功率管T1的反并联的第一二极管有电流流过时，所述控制器控制所述第三功率管T1以所述第五占空比导通，同时，所述控制器保持所述第四功率管T2截止；所述第四功率管T2的反并联的第一二极管有电流流过时，所述控制器控制所述第四功率管T2以第五占空比导通，同时，所述控制器保持所述第三功率管T1截止。
在该技术方案中，在所述供电信号向所述第五功率管T3和第六功率管T4之间的公共端流入时，通过控制所述第五功率管T3和所述第六功率管T4以第四占空比交替导通，且在所述第四功率管T2的反并联的第一二极管有电流流过时，所述控制器控制所述第四功率管T2以第五占空比导通，同时，所述控制器保持所述第三功率管T1截止，实现了对供电信号的功率因数校正处理。
同理，所述第三功率管T1的反并联的第一二极管有电流流过时，所述控制器控制所述第三功率管T1以所述第五占空比导通，同时，所述控制器保持所述第四功率管T2截止，实现了对供电信号的功率因数校正处理。
如图4所示的等效电路可知，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第二功率管Q2设有反并联的第一二极管，所述控制器驱动所述降压型电路以滤波模式工作，具体包括以下步骤：所述控制器控制所述第一功率管Q1导通，所述控制器控制所述第二功率管Q2截止或与所述第一功率管Q1交替导通，所述滤波电路对所述供电信号进行滤波处理。
在该技术方案中，通过所述控制器控制所述第二功率管Q2截止，第二功率管Q2及其反并联的第一二极管均截止，或第二功率管Q2与第一功率管Q1交替导通，此时仅通过所述滤波电路对所述供电信号进行滤波处理，以滤除噪声信号对负载的干扰。
在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述控制器驱动所述降压型电路以降压模式工作，具体包括以下步骤：所述控制器控制所述第一功率管Q1以第六占空比导通，同时，所述控制器控制所述第二功率管Q2与所述第一功率管Q1交替导通。
在该技术方案中，通过所述控制器控制所述第一功率管Q1以第六占空比导通，同时，所述控制器控制所述第二功率管Q2与所述第一功率管Q1交替导通，也即通过第一功率管Q1和第二功率管Q2对母线直流信号进行调制降压处理，以提升负载的效率，另外，有利于降低电机铁损。
需要补充说明的是，如图7所示，本申请还包括以下替代方式：
(1)升压型电路的续流功率管为第五功率管T3和第三功率管T1，分别替换为不控二极管D3和不控二极管D1，不需要进行调制控制。
(2)BUCK电路的第二功率管Q2，替换为不控二极管D2，不需要调制控制。
如图6和图7所示，采用不控二极管替代功率管或开关管，成本更低，但将增加二极管导通损耗(在中低负荷运行情况下，二极管导通压降大于MOSFET的导通压降)。
上述功率管和开关管可以是基于Si材料的MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor,金属氧化物半导体场效应晶体管，简称mos管)、基于SiC材料的MOSFET或者基于GaN材料的MOSFET，另外，桥式电路的四个功率管和第二功率管Q2需要设置反并联的第一二极管或寄生二极管，第一功率管Q1可以不设置反并联的第一二极管。
实施例二：
如图8至图13所示，根据本申请第二方面的实施例，提供了另一种升降压驱动电路，包括：图腾柱电路，所述图腾柱电路被配置为能够对供电信号进行功率因数校正处理或整流处理；降压型电路，所述降压型电路的输入端连接至所述图腾柱电路的输出端，所述降压型电路包括：第一功率管Q1和第二功率管Q2，依次串联于所述图腾柱电路的高压输出端和低压输出端之间，所述第二功率管Q2的两端引出为高压母线和低压母线，其中，控制所述第一功率管Q1和第二功率管Q2交替导通，所述高压母线和低压母线之间的母线电压随着负载运行时长增大而降低，所述降压型电路被配置为能够对所述供电信号进行降压处理或滤波处理。
在该技术方案中，通过在驱动电路中设置图腾柱电路和降压型电路，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
具体地，图腾柱电路和降压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整图腾柱电路和/或降压型电路的工作状态。
其中，供电信号泛指流经驱动电路并驱动负载运行的信号，桥式电路的输入信号为交流信号AC，输出为母线直流信号。因此，在桥式电路的输入端采集交流电流和交流电压，在桥式电路的输出端采集直流电流和直流母线电压。
后文中，所述驱动控制电路的图腾柱电路也可被记作BOOST电路，降压型电路也可被记作BUCK电路。
如图9和图10所示，负载M可以是逆变器IPM及其驱动的永磁电机。
如图10所示，SVPWM的主要思想是以三相对称正弦波电压供电时三相对称电动机定子理想磁链圆为参考标准，以三相逆变器不同开关模式作适当的切换，从而形成PWM波，以所形成的实际磁链矢量来追踪其准确磁链圆。传统的SPWM方法从电源的角度出发，以生成一个可调频调压的正弦波电源，而SVPWM方法将逆变系统和异步电机看作一个整体来考虑，模型比较简单，也便于微处理器的实时控制。
另外，本申请提供的上述技术方案中的升降压驱动电路，还可以具有如下附加技术特征：
在上述技术方案中，进一步地，所述降压型电路包括：滤波电路，所述滤波电路与所述第二功率管Q2并联连接，所述滤波电路用于对流经所述高压母线和所述低压母线的供电信号进行滤波处理。
在该技术方案中，通过将降压型电路设置为包括滤波电路，滤波电路对母线直流信号进行滤波处理，在降压型电路的第一功率管Q1和第二功率管Q2进行调制工作时，实现对母线直流信号的降压处理，不仅有利于提升负载的运行效率，也有利于降低电机的铁损和噪声干扰。
在上述技术方案中，进一步地，所述滤波电路包括：第一感性元件L1，所述 第一感性元件L1的第一端连接于所述第一功率管Q1和所述第二功率管Q2之间的公共端；第一容性元件C1，所述第一容性元件C1的第一端连接于所述第一感性元件L1的第二端，所述第一容性元件C1的第二端连接于所述低压母线。
在该技术方案中，通过将滤波电路设置为包括第一感性元件L1和第一容性元件C1，并按照上述方式连接，即在负载输入端接入LC滤波结构，滤除直流信号中携带的交流噪声，以进一步地提升负载运行的可靠性。
在上述技术方案中，进一步地，所述图腾柱电路包括：第二感性元件L2，所述第二感性元件L2被配置为接入所述供电信号；桥式电路，所述桥式电路的任一桥臂中设有一个功率管，所述桥式电路的输入端连接至所述第二感性元件L2，所述桥式电路被配置为能够对所述供电信号进行功率因数校正处理或整流处理；第二容性元件C2，所述第二容性元件C2连接于所述桥式电路的两个输出端之间。
在该技术方案中，通过设置第二感性元件L2、第二容性元件C2和桥式电路，并且按照上述方式进行连接，一方面，可以作为功率因数校正电路工作，另一方面，可以作为整流电路工作，不仅简化了电路结构，由于桥式电路的每个桥臂设置有功率管，有效地降低了电路功耗和延时。
在上述技术方案中，进一步地，第三功率管T1、第四功率管T2、第五功率管T3和第六功率管T4，所述第三功率管T1与所述第四功率管T2之间的公共端连接至所述第二感性元件L2的第一端，所述供电端的第一输出端与所述第二感性元件L2的第二端相连，所述第五功率管T3与所述第六功率管T4之间的公共端连接至所述供电端的第二输出端，其中，所述第三功率管T1和所述第五功率管T3的公共端作为所述高压输出端，所述第四功率管T2和所述第六功率管T4的公共端作为所述低压输出端。
在该技术方案中，通过将桥式电路设置为具体包括上述四个功率管，且以上述方式进行连接，可以对交流信号AC进行整流处理，另外，在桥式电路的功率管按照指定占空比进行调制升压时，输出的母线直流信号被升高。
如图11所示的等效电路可知，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以二极管整流模式工作，具体包括以下步骤：所述控制器控制所述桥式电路中的功率管均截止，所述反并联的第一二极管对所述供电信号进行整流。
在该技术方案中，所述控制器控制所述桥式电路中的功率管均截止，所述反并联的第一二极管对所述供电信号进行整流，桥式电路等效为二极管整流器，因此，实现对交流信号AC的整流处理。
在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以同步整流模式工作，具体包括以下步骤：所述反并联的第一二极管导通时，所述控制器控制对应的功率管以第一占空比导通。
在该技术方案中，在所述反并联的第一二极管导通时，通过所述控制器控制对应的功率管以第一占空比导通，以实现同步整流处理，响应时间短且可靠性高。
在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以半同步整流模式工作，具体包括以下步骤：控制所述第三功率管T1和所述第四功率管T2截止，所述第五功率管T3的反并联的第一二极管导通时，所述控 制器控制所述第五功率管T3导通，以及所述第六功率管T4的反并联的第一二极管导通时，所述控制器控制所述第六功率管T4导通。
在该技术方案中，通过控制所述第三功率管T1和所述第四功率管T2截止，即第三功率管T1的反并联的第一二极管导通，以及第四功率管T2的反并联的第一二极管导通。
另外，在所述第五功率管T3的反并联的第一二极管导通时，同时，所述控制器控制所述第五功率管T3导通，以及所述第六功率管T4的反并联的第一二极管导通时，所述控制器控制所述第六功率管T4导通，即采用第五功率管T3和第六功率管T4进行同步整流处理。
在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以半同步整流模式工作，具体包括以下步骤：控制所述第五功率管T3和所述第六功率管T4截止，所述第三功率管T1的反并联的第一二极管导通时，所述控制器控制所述第三功率管T1导通，以及所述第四功率管T2的反并联的第一二极管导通时，所述控制器控制所述第四功率管T2导通。
在该技术方案中，控制所述第五功率管T3和所述第六功率管T4截止，即第五功率管T3的反并联的第一二极管导通，以及第六功率管T4的反并联的第一二极管导通。
另外，所述第三功率管T1的反并联的第一二极管导通时，所述控制器控制所述第三功率管T1导通，以及所述第四功率管T2的反并联的第一二极管导通时，所述控制器控制所述第四功率管T2导通，即采用第三功率管T1和第四功率管T2进行同步整流处理。
如图12所示的等效电路可知，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以功率因数校正模式工作，具体包括以下步骤：所述供电信号向所述第三功率管T1和第四功率管T2之间的公共端流入时，所述第三功率管T1和所述第四功率管T2以第二占空比交替导通；所述第五功率管T3的反并联的第一二极管有电流流过时，所述控制器控制所述第五功率管T3以第三占空比导通，同时，所述控制器保持所述第六功率管T4截止；所述第六功率管T4的反并联的第一二极管有电流流过时，所述控制器控制所述第六功率管T4以第三占空比导通，同时，所述控制器保持所述第五功率管T3截止。
在该技术方案中，在所述供电信号向所述第三功率管T1和第四功率管T2之间的公共端流入时，通过控制所述第三功率管T1和所述第四功率管T2以第二占空比交替导通，且在所述第六功率管T4的反并联的第一二极管有电流流过时，所述控制器控制所述第六功率管T4以第三占空比导通，同时，所述控制器保持所述第五功率管T3截止，实现了对供电信号的功率因数校正处理。
同理，所述第五功率管T3的反并联的第一二极管有电流流过时，所述控制器控制所述第五功率管T3以第三占空比导通，同时，所述控制器保持所述第六功率管T4截止，实现了对供电信号的功率因数校正处理。
如图12所示的等效电路可知，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，所述控制器驱动所述桥式电路以功率因数校正模式工作，具体包括以下步骤：所述供电信号向所述第五功率管T3和第六功率管T4之间的公共端流入时，所 述第五功率管T3和所述第六功率管T4以第四占空比交替导通；所述第三功率管T1的反并联的第一二极管有电流流过时，所述控制器控制所述第三功率管T1以所述第五占空比导通，同时，所述控制器保持所述第四功率管T2截止；所述第四功率管T2的反并联的第一二极管有电流流过时，所述控制器控制所述第四功率管T2以第五占空比导通，同时，所述控制器保持所述第三功率管T1截止。
在该技术方案中，在所述供电信号向所述第五功率管T3和第六功率管T4之间的公共端流入时，通过控制所述第五功率管T3和所述第六功率管T4以第四占空比交替导通，且在所述第四功率管T2的反并联的第一二极管有电流流过时，所述控制器控制所述第四功率管T2以第五占空比导通，同时，所述控制器保持所述第三功率管T1截止，实现了对供电信号的功率因数校正处理。
同理，所述第三功率管T1的反并联的第一二极管有电流流过时，所述控制器控制所述第三功率管T1以所述第五占空比导通，同时，所述控制器保持所述第四功率管T2截止，实现了对供电信号的功率因数校正处理。
如图4所示的等效电路可知，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第二功率管Q2设有反并联的第一二极管，所述控制器驱动所述降压型电路以滤波模式工作，具体包括以下步骤：所述控制器控制所述第一功率管Q1导通，所述控制器控制所述第二功率管Q2截止或与所述第一功率管Q1交替导通，所述滤波电路对所述供电信号进行滤波处理。
在该技术方案中，通过所述控制器控制所述第二功率管Q2截止，第二功率管Q2及其反并联的第一二极管均截止，或第二功率管Q2与第一功率管Q1交替导通，此时仅通过所述滤波电路对所述供电信号进行滤波处理，以滤除噪声信号对负载的干扰。
在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述控制器驱动所述降压型电路以降压模式工作，具体包括以下步骤：所述控制器控制所述第一功率管Q1以第六占空比导通，同时，所述控制器控制所述第二功率管Q2与所述第一功率管Q1交替导通。
在该技术方案中，通过所述控制器控制所述第一功率管Q1以第六占空比导通，同时，所述控制器控制所述第二功率管Q2与所述第一功率管Q1交替导通，也即通过第一功率管Q1和第二功率管Q2对母线直流信号进行调制降压处理，以提升负载的效率，另外，有利于降低电机铁损。
需要补充说明的是，如图13所示，本申请还包括以下替代方式：
(1)图腾柱电路的低频开关控制的一侧桥臂为第五功率管T3和第六功率管T4，分别替换为不控二极管D3和不控二极管D4，不需要进行调制控制。
(2)BUCK电路的第二功率管Q2，替换为不控二极管D2，不需要调制控制。
如图12和图13所示，采用不控二极管替代功率管或开关管，成本更低，但将增加二极管导通损耗(在中低负荷运行情况下，二极管导通压降大于MOSFET的导通压降)。
上述功率管和开关管可以是基于Si材料的MOSFET(Metal-Oxide-Semiconductor Field-Effect Transistor,金属氧化物半导体场效应晶体管，简称mos管)、基于SiC材料的MOSFET或者基于GaN材料的MOSFET，另外，桥式电路的四个功率管和第二功率管Q2需要设置反并联的第一二极管，第一功率管Q1可以不设置反并联的第一二极管。
实施例三：
如图14至图27所示，根据本申请第三方面的实施例，提供了再一种升降压驱动电路，包括：降压型电路100，所述降压型电路100包括桥式电路，所述桥式电路的任一桥臂中设有一个功率管，所述降压型电路100被配置为接入供电端输入的供电信号；所述升压型电路200，所述升压型电路200的输入端连接至所述降压型电路100的输出端，所述升压型电路200被配置为能够升高所述供电信号；第七功率管Q11，连接至所述桥式电路的两个输出端，且连接至所述升压型电路的两个输入端，所述第七功率管Q11被配置为能够对所述升压型电路进行续流。
在该技术方案中，通过在驱动电路中设置降压型电路100和升压型电路200，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
如图15、图16和图17所示，供电信号泛指流经驱动电路并驱动负载M运行的信号，桥式电路的输入信号为交流信号AC，输出为母线直流信号。因此，在桥式电路的输入端采集交流电流和交流电压，在桥式电路的输出端采集直流电流和直流母线电压。
具体地，降压型电路100和升压型电路200中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整降压型电路100和/或升压型电路200的工作状态。
后文中，所述驱动控制电路的降压型电路100也可被记作无桥BUCK电路，升压型电路200也可被记作BOOST电路，无桥BUCK电路的输出与BOOST电路的输入直接相连且共用同一个第三感性元件L3，无桥BUCK电路的输入接单相交流电源，BOOST电路的输出接负载M。
如图16和图17所示，负载M可以是逆变器IPM及其驱动的永磁电机。桥式电路的高压输出端连接到第三感性元件L3的一端，桥式电路的低压输出端接BOOST电路的低压输入端，第七功率管Q11的漏极连接到第三感性元件L3的一端，第七功率管Q11的源极连接到桥式电路的低压输出。
如图17所示，SVPWM的主要思想是以三相对称正弦波电压供电时三相对称电动机定子理想磁链圆为参考标准，以三相逆变器不同开关模式作适当的切换，从而形成PWM波，以所形成的实际磁链矢量来追踪其准确磁链圆。传统的SPWM方法从电源的角度出发，以生成一个可调频调压的正弦波电源，而SVPWM方法将逆变系统和异步电机看作一个整体来考虑，模型比较简单，也便于微处理器的实时控制。
另外，本申请提供的上述技术方案中的升降压驱动电路，还可以具有如下附加技术特征：
如图18至图24所示，在上述技术方案中，进一步地，所述桥式电路包括：第一单向导通管T11、第八功率管T12、第二单向导通管T13和第九功率管T14，所述第一单向导通管T11与所述第八功率管T12之间的公共端连接至所述供电端的第一输出端，所述第二单向导通管T13与所述第九功率管T14之间的公共端连接至所述供电端的第二输出端，所述第一单向导通管T11和所述第二单向导通管T13的公共端作为所述桥式电路的高压输出端，所述第八功率管T12和所述第九功率管T14的公共端作为所述桥式电路的低压输出端，其中，所述第一单向导通管T11和第二单向导通管T13均截止，所述第七功率管Q11对所述升压型电路进行续流。
在该技术方案中，通过将桥式电路设置为具体包括上述四个功率管，且以上述方式进行连接，可以对交流信号AC进行整流处理，另外，在桥式电路的输出端设置第七功率管Q11，第七功率管Q11导通时，整流后的直流信号不能传输至下一级的升压型电路200，第七功率管Q11截止时，桥式电路输出的直流信号传输至升压型电路200，可以经升压型电路200继续进行调制升压。
其中，第一单向导通管T11和第二单向导通管T13对供电信号进行斩波，以对母线电压进行降压调制。
如图14至图21所示，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第八功率管T12设有反并联的第二二极管，所述第九功率管T14均设有反并联的第三二极管，所述控制器驱动所述桥式电路以二极管整流模式工作，具体包括以下步骤：所述控制器控制所述第八功率管T12和所述第九功率管T14均截止，所述第二二极管和所述第三二极管对所述供电信号进行整流，其中，所述第一单向导通管T11的漏极电压高于源极电压，所述第一单向导通管T7导通，所述第二单向导通管T13的漏极电压高于源极电压，所述第二单向导通管T13导通。
在该技术方案中，在控制器驱动桥式电路进行整流时，通过控制所述第八功率管T12和所述第九功率管T14均截止，所述第二二极管和所述第三二极管对所述供电信号进行整流，其中，所述第一单向导通管T11的漏极电压高于源极电压，所述第一单向导通管T11导通，所述第二单向导通管T13的漏极电压高于源极电压，所述第二单向导通管T13导通。
另外，在上述整流过程中，第一单向导通管T11和第二二极管的导通方向相同，第二单向导通管T13和第三二极管的导通方向相同，考虑到其单向导通作用，第九功率管T14和第八功率管T12均可以被替代为二极管。
如图14至图21所示，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第八功率管T12设有反并联的第二二极管，所述第九功率管T14设有反并联的第三二极管，所述控制器驱动所述桥式电路以同步整流模式工作，具体包括：所述第一单向导通管T11的漏极电压高于源极电压，所述第一单向导通管T11导通，同时，所述第九功率管T14导通，所述第二单向导通管T13的漏极电压高于源极电压，所述第二单向导通管T13导通，同时，所述第八功率管T12导通。
在该技术方案中，通过控制器驱动所述桥式电路以同步整流模式工作，既所述第一单向导通管T11的漏极电压高于源极电压，所述第一单向导通管T11导通，同时，所述第九功率管T14导通，此时，通过第一单向导通管T11和第九功率管T4输出供电信号，响应时间短且可靠性高。
同理，所述第二单向导通管T13的漏极电压高于源极电压，所述第二单向导通管T13导通，同时，所述第八功率管T12导通，因此通过第八功率管T12和第二单向导通管T13输出供电信号，响应时间短且可靠性高。
如图14至图21所示，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第八功率管T12设有反并联的第二二极管，所述第九功率管T14设有反并联的第三二极管，所述控制器驱动所述桥式电路以二极管整流降压模式工作，具体包括：所述控制器控制所述第八功率管T12和所述第九功率管T14均截止，所述第二二极管和所述第三二极管对所述供电信号进行整流；所述第一单向导通管T11的漏极电压高于源极电压，所述控制器触发所述 第一单向导通管T11按照第一占空比导通或截止，所述第二单向导通管T13的漏极电压高于源极电压，所述控制器触发所述第二单向导通管T13按照第二占空比导通或截止。
在该技术方案中，所述控制器驱动所述桥式电路以二极管整流降压模式工作，进行二极管整流时，通过所述控制器控制所述第八功率管T12和所述第九功率管T14均截止，所述第二二极管和所述第三二极管对所述供电信号进行整流，所述第一单向导通管T11的漏极电压高于源极电压，所述控制器触发所述第一单向导通管T11按照第一占空比导通或截止，所述第二单向导通管T13的漏极电压高于源极电压，所述控制器触发所述第二单向导通管T13按照第二占空比导通或截止。
其中，第一单向导通管T11和第二单向导通管T13依次工作于交流电压的两个半周期内，为了提高功率器件的可靠性，在第一单向导通管T11和第二单向导通管T13之间的切换时段设置有一个死区时间。
另外，在交流电压高于直流母线电压的给定值时，控制器可以触发第七功率管Q11以指定占空比进行降压调制，同时，升压型电路200以滤波模式工作，而不进行升压调制，以提高驱动电路的效率。
如图14至图21所示，在上述任一技术方案中，进一步地，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第八功率管T12设有反并联的第二二极管，所述第九功率管T14设有反并联的第三二极管，所述控制器驱动所述桥式电路以同步整流降压模式工作，具体包括：所述第一单向导通管T11的漏极电压高于源极电压，所述第九功率管T14导通，同时，所述控制器控制所述第一单向导通管T11按照第三占空比导通或截止，所述第二单向导通管T13的漏极电压高于源极电压，所述第八功率管T12导通，同时，所述控制器控制所述第二单向导通管T13按照第四占空比导通或截止。
在该技术方案中，所述控制器驱动所述桥式电路以同步整流降压模式工作，通过所述第一单向导通管T11的漏极电压高于源极电压，所述第九功率管T14导通，同时，所述控制器控制所述第一单向导通管T11按照第三占空比导通或截止，所述第二单向导通管T13的漏极电压高于源极电压，所述第八功率管T12导通，同时，所述控制器控制所述第二单向导通管T13按照第四占空比导通或截止。
其中，在交流电压的第一半周期内，检测到交流电压的绝对值高于直流母线电压的给定值时，第九功率管T14导通，且第一单向导通管T11开始调制工作，在交流电压的第二半周期内，检测到交流电压的绝对值高于直流母线电压的给定值时，第八功率管T12导通，且第二单向导通管T13开始调制工作。
另外，第一单向导通管T11和第二单向导通管T13依次工作于交流电压的两个半周期内，为了提高功率器件的可靠性，在第一单向导通管T11和第二单向导通管T13之间的切换时段设置有一个死区时间。
另外，第八功率管T12和第九功率管T14依次工作于交流电压的两个半周期内，为了提高功率器件的可靠性，在第八功率管T12和第九功率管T14之间的切换时段设置有一个死区时间。
在上述任一技术方案中，进一步地，还包括：所述第一单向导通管T11和所述第九功率管T14中的一个功率管为反向阻断开关管或绝缘栅门极晶体管，所述第一单向导通管T11和所述第九功率管T14中的另一个功率管为不控二极管或金属氧化物半导体管；以及所述第八功率管T12和所述第二单向导通管T13中的一个功率管为反向阻断开关管或绝缘栅门极晶体管，所述第八功率管T12和所述第二单向导通 管T13中的另一个功率管为不控二极管或金属氧化物半导体管。
在该技术方案中，可以设置第八功率管T12和第九功率管T14中的一个可调制工作的反向阻断开关管或绝缘栅门极晶体管，另一个为不控二极管或金属氧化物半导体管，有利于降低驱动电路的功耗和可靠性。
如图25和图26所示，在上述任一技术方案中，进一步地，所述反向阻断开关管包括：第一N沟道金属氧化物半导体管和第二N沟道金属氧化物半导体管，两个所述N沟道金属氧化物半导体管的漏极相接；比较器，所述第一N沟道金属氧化物半导体管的源极连接至所述比较器的第一输入端，所述第二N沟道金属氧化物半导体管的源极连接至所述比较器的第二输入端；控制器，所述控制器的输入端连接至所述比较器的输出端，所述控制器的输出端连接至所述N沟道金属氧化物半导体管的栅极。
在该技术方案中，反向阻断开关的关键部件为比较器和两个反串连的金属氧化物半导体管，其中，所述第一N沟道金属氧化物半导体管的源极连接至所述比较器的第一输入端，所述第二N沟道金属氧化物半导体管的源极连接至所述比较器的第二输入端，通过比较器的输出结果来控制金属氧化物半导体管导通或截止，基于此，设置反向阻断开关来克服二极管压降大和功耗大等问题，且响应效率高。
在上述任一技术方案中，进一步地，所述反向阻断开关管包括：第一P沟道金属氧化物半导体管和第二P沟道金属氧化物半导体管，两个所述P沟道金属氧化物半导体管的源极相接；比较器，所述第一P沟道金属氧化物半导体管的漏极连接至所述比较器的第一输入端，所述第二P沟道金属氧化物半导体管的漏极连接至所述比较器的第二输入端；控制器，所述控制器的输入端连接至所述比较器的输出端，所述控制器的输出端连接至所述P沟道金属氧化物半导体管的栅极。
具体地，上述两个P型MOS开关管反向串联、反并联二极管的正极相连，增加比较器和驱动器。比较器比较两个MOS管上下端的电压，当上端A电压高于下端B电压时，关闭驱动器，MOS管处于关闭状态，当下端B电压高于上端A电压时，使能驱动器，使开关管可以被控制信号控制，实现导通和关断。
在该技术方案中，反向阻断开关的关键部件为比较器和两个反串连的金属氧化物半导体管，其中，所述第一P沟道金属氧化物半导体管的源极连接至所述比较器的第一输入端，所述第二P沟道金属氧化物半导体管的源极连接至所述比较器的第二输入端，通过比较器的输出结果来控制金属氧化物半导体管导通或截止，基于此，设置反向阻断开关来克服二极管压降大和功耗大等问题，且响应效率高。
具体地，上述两个N型MOS开关管反向串联、反并联二极管的负极相连，增加比较器和驱动器。比较器比较两个MOS管上下端的电压，当上端A电压高于下端B电压时，关闭驱动器，MOS管处于关闭状态；当下端B电压高于上端A电压时，使能驱动器，使开关管可以被控制信号控制，实现导通和关断。
在上述任一技术方案中，进一步地，所述反向阻断开关管包括：串联的二极管D0和金属氧化物半导体管，所述金属氧化物半导体管设有反并联的二极管，所述二极管D0的导通方向与所述反并联的二极管的导通方向相反。
在该技术方案中，通过设置反向阻断开关管包括串联的二极管D0和金属氧化物半导体管，所述金属氧化物半导体管设有反并联的二极管，所述二极管D0的导通方向与所述反并联的二极管的导通方向相反，在金属氧化物半导体管截止时，其串联的二极管D0和反并联的二极管由于导通方向相反，也是截止的，基于此，来克服二极管压降大和功耗大等问题，且响应效率高。
如图27所示，N沟道金属氧化物半导体管包括栅极G、源极S和漏极D，源极S连接至二极管D0的阳极。
在上述任一技术方案中，进一步地，所述升压型电路200包括：第三感性元件L3，所述第三感性元件L3的第一端连接至所述桥式电路的高压输出端；第十功率管Q13，连接于所述第三感性元件L3的第二端与所述桥式电路的低压输出端之间；第十一功率管Q12，连接于所述第三感性元件L3的第二端与第三容性元件C3的第一端之间，所述第三容性元件C3的第二端连接至所述低压输出端，控制器，所述控制器连接至所述第十功率管Q13的控制端和所述第十一功率管Q12的控制端，所述控制器控制所述升压型电路200以升压模式运行，具体包括：所述控制器根据所述高压输出端和所述低压输出端之间的母线电压对应的电压给定值和所述母线电压确定第五占空比，所述控制器按照所述第五占空比控制所述第十功率管Q13导通或截止，第十一功率管Q12与所述第十功率管Q13交替导通或保持截止。
在该技术方案中，通过将升压型电路200设置为包括第三感性元件L3、第十功率管Q13和第十一功率管Q12，其中，所述控制器根据所述高压输出端和所述低压输出端之间的母线电压对应的电压给定值和所述母线电压确定第五占空比，所述控制器按照所述第五占空比控制所述第十功率管Q13导通或截止，此时，升压型电路200对母线直流电压进行升压调制，以满足负载M的运行需求和可靠性。
在上述任一技术方案中，进一步地，所述升压型电路200包括：第三感性元件L3，所述第三感性元件L3的第一端连接至所述桥式电路的高压输出端；第十功率管Q13，连接于所述第三感性元件L3的第二端与所述桥式电路的低压输出端之间；第十一功率管Q12，连接于所述第三感性元件L3的第二端与第三容性元件C3的第一端之间，所述第三容性元件C3的第二端连接至所述低压输出端；控制器，所述控制器连接至所述第十功率管Q13的控制端和所述第十一功率管Q12的控制端，所述控制器控制所述升压型电路200以滤波模式运行，具体包括：所述控制器控制所述第十一功率管Q12导通，所述控制器控制所述第十功率管Q13截止。
在该技术方案中，通过将升压型电路200设置为包括第三感性元件L3、第十功率管Q13和第十一功率管Q12，其中，所述控制器控制所述第十一功率管Q12导通，所述控制器控制所述第十功率管Q13截止，此时，升压型电路200对母线直流电压进行直通滤波，以降低驱动电路中的纹波噪声。
所述BOOST电路包括第十功率管Q13、第十一功率管Q12、第三感性元件L3和第三容性元件C3，第十一功率管Q12的源极和第十功率管Q13的漏极接第三感性元件L3的一端，第十功率管Q13的源极与桥式电路的低压输出、第一电解电容的负极相连，第十一功率管Q12的漏极与第三容性元件C3的正极相连。
第一单向导通管T11和第二单向导通管T13可以是反向阻断功率开关管，也可以是没有反并联二极管的IGBT(Insulated Gate Bipolar Transistor，绝缘栅双极型晶体管)或者反向阻断功率开关管实现的电路模块，第八功率管T12、第九功率管14、第七功率管Q11和第十一功率管Q12是双向导通功率开关管，可以是基于Si材料的MOSFET(Metal-Oxide-Semiconductor Field-Effect Transistor,金属氧化物半导体场效应晶体管，简称mos管)、基于SiC材料的MOSFET或者基于GaN材料的MOSFET，第十功率管Q3可以是功率开关管，可以是IGBT，也可以是基于Si材料的MOSFET、基于SiC材料的MOSFET或者基于GaN材料的MOSFET。其中，第八功率管T12、第九功率管T14、第一功率管Q1、第十功率管Q13和第十一功率管Q12需要具有反并联二极管，譬如，寄生二极管或外部并联二极管，第一单向 导通管T11和第二单向导通管T13均没有反并联二极管。
另外，上述驱动电路还包括其他等效替代方案，具体如下：
(1)如图18所示，无桥BOOST电路的第八功率管T12、第十功率管Q13和第七功率管Q11可以替换为不控二极管，不需要控制导通或截止。
(2)如图20所示，无桥BOOST电路的第十功率管Q13可以替换为不控二极管，不需要控制。
综上，采用不控二极管，成本更低，但将增加二极管导通损耗尤其在中低负荷运行情况下，二极管导通压降大于MOSFET的导通压降。
所述驱动控制电路的无桥BUCK电路，其中第一单向导通管T11和第九功率管T14一组，第八功率管T2和第二单向导通管T13是一组。
如图23所示，上述控制逻辑是基于第一单向导通管T11是反向阻断功率开关管、第九功率管T14是双向导通功率开关管的。如图22和图24所示，如果第九功率管T14是反向阻断功率开关管、第一单向导通管T11是双向导通功率开关管，则控制第一单向导通管T11和第九功率管T14的控制逻辑对调。
如图22所示，上述控制逻辑是基于第二单向导通管T13是反向阻断功率开关管、第八功率管T12是双向导通功率开关管的。如图23和图24所示，如果第八功率管T12是反向阻断功率开关管、第二单向导通管T13是双向导通功率开关管，则控制第八功率管T12和第二单向导通管T13的控制逻辑对调。
实施例四：
如图44所示，根据本申请第四方面的实施例，提供了一种升降压驱动方法，包括：步骤S302，确定输入至所述驱动电路的交流电压，以及所述驱动电路的母线电压；步骤S304，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作。
在该技术方案中，在驱动电路中设置升压型电路和降压型电路，根据所述交流电压和所述母线电压，通过控制所述升压型电路以整流模式或功率因数校正模式工作，以及控制所述降压型电路以降压模式或滤波模式工作，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
其中，供电信号泛指流经驱动电路并驱动负载运行的信号，桥式电路的输入信号为交流信号，输出为母线直流信号。因此，在桥式电路的输入端采集交流电流和交流电压，在桥式电路的输出端采集直流电流和直流母线电压。
具体地，升压型电路和降压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整升压型电路和/或降压型电路的工作状态。
在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，具体包括：确定母线电压对应的电压给定值；比较所述电压给定值与所述交流电压之间的大小关系；根据所述电压给定值与所述交流电压之间的大小关系，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作。
在该技术方案中，通过根据所述电压给定值与所述交流电压之间的大小关系，进而控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，为了提高驱动电路的工作效率，在降压型电路以降压模式工作时，升压型电路以整流模式工作，或者，升压型电路以功率因数校正模式工作时，降压型电路以滤波模式工作，另外，降压型电路以滤波模式工作，同时，升压型电路可以以整流模式工作。
在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，具体包括：确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；检测到所述第一电压采样值大于或等于母线电压对应的电压给定值，检测所述交流电压的瞬时值；检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述升压型电路以整流模式工作，控制所述降压型电路以滤波模式工作；检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述升压型电路以整流模式工作，控制所述降压型电路以降压模式工作。
在该技术方案中，通过确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值，若检测到所述第一电压采样值大于或等于母线电压对应的电压给定值，则检测所述交流电压的瞬时值，说明此时母线电压较高，足够驱动负载可靠地运行。
若检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，则控制所述升压型电路以整流模式工作，控制所述降压型电路以滤波模式工作，仍然不需要进行升压或降压处理，不需要控制功率管、第一功率管和第二功率管进行调制工作，有利于降低驱动电路的整机功耗。
进一步地，检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述升压型电路以整流模式工作，控制所述降压型电路以降压模式工作。
如图28所示，在电压不控制模式下，升压型电路工作于二极管整流或同步整流状态，降压型电路工作于直通滤波状态。
如图29所示，在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，具体包括：确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，检测所述交流电压的瞬时值；检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述升压型电路以功率因数校正模式工作，控制所述降压型电路以滤波模式工作；检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述升压型电路以整流模式工作，控制所述降压型电路以降压模式工作。
在该技术方案中，第一电压采样值小于第二电压采样值，若检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，则继续预测检测交流电压升高的趋势，因此，继续检测所述交流电压的瞬时值。
进一步的，若检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述升压型电路以功率因数校正模式工作，以提升供电效率，另外，通过控制所述降压型电路以滤波模式工作，以进一步地滤除供电信号中的噪声，以提升负载运行的可靠性。
如图30所示，在上述任一技术方案中，进一步地，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，具体包括：确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述升压型电路以功率因数校正模式工作。
在该技术方案中，检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述升压型电路以升压模式工作，也即通过及时升压来降低直流母线电压的跌落和电机停机的可能性。
其中，在升压模式下，降压型电路处于滤波状态，同时，升压型电路工作于升压调制状态。
在上述任一技术方案中，进一步地，所述电机为永磁式同步电机，所述驱动方法还包括：确定所述永磁式同步电机的转速和反电动势系数；根据所述转速和所述反电动势系数确定所述母线电压对应的电压给定值。
在该技术方案中，通过反电动势系数确定母线电压对应的电压给定值，有利于进一步地提升对直流母线电压进行升降压调节的可靠性和灵活性。
如图31和图34所示，当升压型电路工作在二极管整流和同步整流状态时，BUCK电路既可以工作在直通滤波状态，也可以工作在BUCK降压控制状态；当升压型电路工作在升压PFC控制状态时，BUCK电路只能工作在直通滤波状态。
其中，升压型电路的工作状态包括二极管整流、同步整流和升压PFC控制。
二极管整流状态，即四个功率开关管都处于关断状态，利用其反并联二极管进行整流。
同步整流状态，即四个功率开关管都处于低频开关状态，对于其中一侧桥臂(例如T1和T3)，当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管；对于另外一侧桥臂(例如T2和T4)，当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断。
升压PFC控制状态，一侧桥臂(例如T1和T2)为高频开关控制、实现升压调节功能，根据直流母线电压给定值和检测值、以及交流输入电压检测与交流输入电流检测进行闭环控制另一侧桥臂的第六功率管T4为低频开关控制、实现同步整流功能，即当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断，另一侧桥臂的第五功率管T3关闭。
当处于电压负半周期时，通过一侧桥臂(例如T3和T4)高频开关控制、实现升压调节功能，根据直流母线电压给定值和检测值、以及交流输入电压检测与交流输入电流检测进行闭环控制。另一侧桥臂的第四功率管T2为低频开关控制、实现同步整流功能，即当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断，另一侧桥臂的第三功率管T1关闭。
如图32、图36和图40所示，半同步整流一，即对于其中一侧桥臂(例如T1 和T3)都处于关断状态，利用其反并联二极管进行整流；对于另外一侧桥臂(例如T2和T4)，当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断。
如图33、图37和图39所示，半同步整流二，即对于其中一侧桥臂(例如T1和T3)，当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断；对于另外一侧桥臂(例如T2和T4)都处于关断状态，利用其反并联二极管进行整流。
其中，BUCK电路的工作状态包括直通滤波和BUCK降压控制。
如图39、图40、图41、图42和43所示，直通滤波状态下，控制第三功率管T1持续导通、第四功率管T2持续关断，达到电流直通并经过LC滤波。
BUCK降压控制状态，通过控制第三功率管T1、实现降压调节功能，根据直流母线电压给定值和检测值进行闭环控制。当第三功率管T1导通时，控制第四功率管T2关断。当第三功率管T1关断时，控制第四功率管T2导通或者关断。
如图35和图38所示，电压不控制模式时，升压型电路工作在二极管整流状态或者同步整流状态(次选半同步整流)，BUCK电路工作在直通滤波状态(相当于Π型滤波器)。
降压控制模式时，升压型电路工作在二极管整流状态或者同步整流状态(次选半同步整流)，BUCK电路工作在BUCK降压控制状态。
如图43所示，升压控制模式时，升压型电路工作在升压PFC控制状态，BUCK电路工作在直通滤波状态(相当于Π型滤波器)。
根据直流母线电压给定与交流电压之间的关系，确定一个周期内工作模式切换，具体包括以下几种方式：
1)如果直流母线电压给定≤交流电压有效值×第一电压系数：瞬时交流电压绝对值小于直流母线电压给定时进入电压不控制模式，否则进入降压控制模式。
2)如果交流电压有效值×第一电压系数≤直流母线电压给定≤交流电压有效值×第二电压系数：瞬时交流电压绝对值小于直流母线电压给定时进入升压控制模式，否则进入降压控制模式。
3)如果直流母线电压给定≥交流电压有效值×第二电压系数：升压控制模式，没有模式切换。
4)第一电压系数≤1.4，第二电压系数≥1.0，第一电压系数≤第二电压系数。
在永磁同步电机变频驱动作为负载的应用场景中，直流母线电压给定根据永磁同步电机的转速及其相电压反电势系数确定，直流母线电压给定＝转速×相电压反电势系数×第三电压系数。
其中，1≤第三电压系数≤2.5。
另外，1.5≤第三电压系数≤2。
实施例五：
如图54所示，根据本申请第五方面的实施例，提供了另一种升降压驱动方法，包括：步骤S302，确定输入至所述驱动电路的交流电压，以及所述驱动电路的母线电压；步骤S304，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作。
在该技术方案中，在驱动电路中设置图腾柱电路和降压型电路，根据所述交流电压和所述母线电压，通过控制所述图腾柱电路以整流模式或功率因数校正模式工作，以及控制所述降压型电路以降压模式或滤波模式工作，实现了对母线电压的升降压调节，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
其中，供电信号泛指流经驱动电路并驱动负载运行的信号，桥式电路的输入信号为交流信号，输出为母线直流信号。因此，在桥式电路的输入端采集交流电流和交流电压，在桥式电路的输出端采集直流电流和直流母线电压。
具体地，图腾柱电路和降压型电路中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整图腾柱电路和/或降压型电路的工作状态。
在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，具体包括：确定母线电压对应的电压给定值；比较所述电压给定值与所述交流电压之间的大小关系；根据所述电压给定值与所述交流电压之间的大小关系，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作。
在该技术方案中，通过根据所述电压给定值与所述交流电压之间的大小关系，进而控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，为了提高驱动电路的工作效率，在降压型电路以降压模式工作时，图腾柱电路以整流模式工作，或者，图腾柱电路以功率因数校正模式工作时，降压型电路以滤波模式工作，另外，降压型电路以滤波模式工作，同时，图腾柱电路可以以整流模式工作。
在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，具体包括：确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；检测到所述第一电压采样值大于或等于母线电压对应的电压给定值，检测所述交流电压的瞬时值；检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述图腾柱电路以整流模式工作，控制所述降压型电路以滤波模式工作；检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述图腾柱电路以整流模式工作，控制所述降压型电路以降压模式工作。
在该技术方案中，通过确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值，若检测到所述第一电压采样值大于或等于母线电压对应的电压给定值，则检测所述交流电压的瞬时值，说明此时母线电压较高，足够驱动负载可靠地运行。
若检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，则控制所述图腾柱电路以整流模式工作，控制所述降压型电路以滤波模式工作，仍然不需要进行升压或降压处理，不需要控制功率管、第一功率管和第二功率管进行调制工作，有利于降低驱动电路的整机功耗。
进一步地，检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压 给定值，控制所述图腾柱电路以整流模式工作，控制所述降压型电路以降压模式工作。
如图28所示，在电压不控制模式下，图腾柱电路工作于二极管整流或同步整流状态，降压型电路工作于直通滤波状态。
如图29所示，在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，具体包括：确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，检测所述交流电压的瞬时值；检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述图腾柱电路以功率因数校正模式工作，控制所述降压型电路以滤波模式工作；检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述图腾柱电路以整流模式工作，控制所述降压型电路以降压模式工作。
在该技术方案中，第一电压采样值小于第二电压采样值，若检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，则继续预测检测交流电压升高的趋势，因此，继续检测所述交流电压的瞬时值。
进一步的，若检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述图腾柱电路以功率因数校正模式工作，以提升供电效率，另外，通过控制所述降压型电路以滤波模式工作，以进一步地滤除供电信号中的噪声，以提升负载运行的可靠性。
如图30所示，在上述任一技术方案中，进一步地，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，具体包括：确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述图腾柱电路以功率因数校正模式工作。
在该技术方案中，检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述图腾柱电路以升压模式工作，也即通过及时升压来降低直流母线电压的跌落和电机停机的可能性。
其中，在升压模式下，降压型电路处于滤波状态，同时，图腾柱电路工作于升压调制状态。
在上述任一技术方案中，进一步地，所述电机为永磁式同步电机，所述驱动方法还包括：确定所述永磁式同步电机的转速和反电动势系数；根据所述转速和所述反电动势系数确定所述母线电压对应的电压给定值。
在该技术方案中，通过反电动势系数确定母线电压对应的电压给定值，有利于进一步地提升对直流母线电压进行升降压调节的可靠性和灵活性。
如图31和图35所示，当图腾柱电路工作在二极管整流和同步整流状态时，BUCK电路既可以工作在直通滤波状态，也可以工作在BUCK降压控制状态；当图腾柱电路工作在升压PFC控制状态时，BUCK电路只能工作在直通滤波状态。
其中，图腾柱电路的工作状态包括二极管整流、同步整流和升压PFC控制。
二极管整流状态，即四个功率开关管都处于关断状态，利用其反并联二极管进 行整流。
同步整流状态，即四个功率开关管都处于低频开关状态，对于其中一侧桥臂(例如T1和T2)，当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管；对于另外一侧桥臂(例如T3和T4)，当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断。
升压PFC控制状态，一侧桥臂(例如T1和T2)为高频开关控制、实现升压调节功能，根据直流母线电压给定值和检测值、以及交流输入电压检测与交流输入电流检测进行闭环控制；另一侧桥臂(例如T3和T4)为低频开关控制、实现同步整流功能，即当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断。
如图45、图47和图52所示，半同步整流一，即对于其中一侧桥臂(例如T1和T2)都处于关断状态，利用其反并联二极管进行整流；对于另外一侧桥臂(例如T3和T4)，当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断。
如图33、图48和图51所示，半同步整流二，即对于其中一侧桥臂(例如T1和T2)，当功率开关管的反并联二极管有电流流过时、才开通当前功率开关管，或者，当功率开关管的反并联二极管有电流流过的半周期内开通当前功率开关管、另外半个周期时间关断；对于另外一侧桥臂(例如T3和T4)都处于关断状态，利用其反并联二极管进行整流。
其中，BUCK电路的工作状态包括直通滤波和BUCK降压控制。
如图50、图51、图52和图53所示，直通滤波状态，控制第一功率管Q1持续导通、第二功率管Q2持续关断，达到电流直通并经过LC滤波。
BUCK降压控制状态，通过控制第一功率管Q1、实现降压调节功能，根据直流母线电压给定值和检测值进行闭环控制。当第一功率管Q1导通时，控制第二功率管Q2关断；当第一功率管Q1关断时，控制第二功率管Q2导通或者关断。
如图46和图49所示，电压不控制模式时，图腾柱电路工作在二极管整流状态或者同步整流状态(次选半同步整流)，BUCK电路工作在直通滤波状态(相当于Π型滤波器)。
降压控制模式时，图腾柱电路工作在二极管整流状态或者同步整流状态(次选半同步整流)，BUCK电路工作在BUCK降压控制状态；
如图53所示，升压控制模式时，图腾柱电路工作在升压PFC控制状态，BUCK电路工作在直通滤波状态(相当于Π型滤波器)。
根据直流母线电压给定与交流电压之间的关系，确定一个周期内工作模式切换，具体包括以下几种方式：
1)如果直流母线电压给定≤交流电压有效值×第一电压系数：瞬时交流电压绝对值小于直流母线电压给定时进入电压不控制模式，否则进入降压控制模式。
2)如果交流电压有效值×第一电压系数≤直流母线电压给定≤交流电压有效值×第二电压系数：瞬时交流电压绝对值小于直流母线电压给定时进入升压控制模式，否则进入降压控制模式。
3)如果直流母线电压给定≥交流电压有效值×第二电压系数：升压控制模式， 没有模式切换。
4)第一电压系数≤1.4，第二电压系数≥1.0，第一电压系数≤第二电压系数。
在永磁同步电机变频驱动作为负载的应用场景中，直流母线电压给定根据永磁同步电机的转速及其相电压反电势系数确定，直流母线电压给定＝转速×相电压反电势系数×第三电压系数。
其中，1≤第三电压系数≤2.5；优选地，1.5≤第三电压系数≤2。
实施例六：
如图63所示，根据本申请第六方面的实施例，提供了再一种升降压驱动方法，包括：步骤S302，确定输入至所述驱动电路的交流电压，以及所述驱动电路的母线电压；步骤S304，根据所述交流电压和所述母线电压，控制所述降压型电路100以整流模式或降压模式工作，以及控制所述升压型电路200以升压模式或滤波模式工作。
在该技术方案中，在驱动电路中设置降压型电路100和升压型电路200，根据所述交流电压和所述母线电压，通过控制所述降压型电路100以整流模式或降压模式工作，以及控制所述升压型电路200以升压模式或滤波模式工作，实现了对母线电压的升降压调节，如图29和图30所示，既可以使母线电压高于交流电压峰值，也可以使母线电压低于交流电压峰值，以提升电机效率和可靠性，尤其对永磁同步电机而言，可以通过降低母线电压来降低电机的铁损。
其中，供电信号泛指流经驱动电路并驱动负载M运行的信号，桥式电路的输入信号为交流信号AC，输出为母线直流信号。因此，在桥式电路的输入端采集交流电流和交流电压，在桥式电路的输出端采集直流电流和直流母线电压。
具体地，降压型电路100和升压型电路200中设置有多个半导体开关，半导体开关受控于一个控制器，控制器根据上述采集的交流电压、交流电流、直流母线电压和直流母线电流中的至少一个信号，调制半导体开关的工作状态，进而调整降压型电路100和/或升压型电路200的工作状态。
下面举例说明驱动电路的各种工作模式，具体如下：
(1)当无桥BUCK电路工作在二极管整流和同步整流状态时，BOOST电路既可以工作在直通滤波状态，也可以工作在BOOST升压控制状态；当无桥BUCK电路工作在BUCK降压控制状态时，BOOST电路只能工作在直通滤波状态。
(2)无桥BUCK电路的工作状态包括二极管整流、同步整流、二极管整流+BUCK降压控制(如图57所示)、同步整流+BUCK降压控制(如图20所示)。
(3)二极管整流状态：第八功率管T12和第九功率管T14都处于关断状态，利用其反并联二极管进行整流，第一单向导通管T11在第一单向导通管T11漏极电压高于源极电压时开通、反之关断，第二单向导通管T13在第二单向导通管T13漏极电压高于源极电压时开通、反之关断。
(4)同步整流状态：第一单向导通管T11在第一单向导通管T11漏极电压高于源极电压时开通、反之关断，第二单向导通管T13在第二单向导通管T13漏极电压高于源极电压时开通、反之关断；第八功率管T12在第二单向导通管T13漏极电压高于源极电压时开通、反之关断；第九功率管T14在第一单向导通管T11漏极电压高于源极电压时开通、反之关断。
(5)二极管整流+BUCK降压控制状态：第一单向导通管T11在第一单向导通管T11漏极电压高于源极电压时进行PWM占空比调节控制，第二单向导通管T13在第二单向导通管T13漏极电压高于源极电压时PWM占空比调节控制；第八功率 管T12和第九功率管T14都处于关断状态。
(6)同步整流+BUCK降压控制状态：第一单向导通管T11在第一单向导通管T11漏极电压高于源极电压时进行PWM占空比调节控制，第二单向导通管T13在第二单向导通管T13漏极电压高于源极电压时PWM占空比调节控制；第八功率管T12在第二单向导通管T13漏极电压高于源极电压时开通、反之关断；第九功率管T14在第一单向导通管T11漏极电压高于源极电压时开通、反之关断。
如图57所示，二极管整流+BUCK降压+LC滤波模式下功率开关器件开关状态。
如图58所示，同步整流+BUCK降压+LC滤波模式下功率开关器件开关状态。
如图59所示，(二极管整流+BUCK降压+LC滤波)与(二极管整流+BOOST升压)两种模式切换下的功率开关器件开关状态示意图。
如图60所示，(同步整流+BUCK降压+LC滤波)与(同步整流+BOOST升压)两种模式切换下的功率开关器件开关状态示意图。
如图61所示，二极管整流+BOOST升压模式下的功率开关器件开关状态。
如图62所示，同步整流+BOOST升压模式下的功率开关器件开关状态。
另外，BOOST电路的工作状态包括直通滤波和BUCK降压控制，具体如下：
(1)直通滤波状态：控制功率开关管第十一功率管Q12持续导通、功率开关管第十功率管Q13持续关断，达到直通LC滤波。
(2)BOOST升压控制状态：通过控制功率开关管第十功率管Q13、实现升压调节功能，根据直流母线电压给定值和检测值进行闭环控制。当功率开关管第十功率管Q13导通时，控制功率开关管第十一功率管Q12关断；当功率开关管第十功率管Q13关断时，控制功率开关管第十一功率管Q12导通或者关断。
驱动电路的不控制模式包括以下：
(1)电压不控制模式时，无桥BUCK电路工作在二极管整流状态(如图55所示)或者同步整流状态(如图56所示)，BOOST电路工作在直通滤波状态，相当于LC滤波器。
(2)降压控制模式时，无桥BUCK电路工作在二极管整流+BUCK降压控制状态或者同步整流+BUCK降压控制状态，BOOST电路工作在直通滤波状态，相当于LC滤波器。
(3)升压控制模式时，无桥BUCK电路工作在升压二极管整流状态或者同步整流状态，BOOST电路工作在BOOST升压控制状态。
在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路100以整流模式或降压模式工作，以及控制所述升压型电路200以升压模式或滤波模式工作，具体包括：确定母线电压对应的电压给定值；比较所述电压给定值与所述交流电压之间的大小关系；根据所述电压给定值与所述交流电压之间的大小关系，控制所述降压型电路100以整流模式或降压模式工作，以及控制所述升压型电路200以升压模式或滤波模式工作。
在该技术方案中，通过根据所述电压给定值与所述交流电压之间的大小关系，进而控制所述降压型电路100以整流模式或降压模式工作，以及控制所述升压型电路200以升压模式或滤波模式工作，为了提高驱动电路的工作效率，在降压型电路100以降压模式工作时，升压型电路200以滤波模式工作，或者，升压型电路200以升压模式工作时，降压型电路100以整流模式工作，另外，降压型电路100以整流模式工作，同时，升压型电路可以以滤波模式工作。
在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制 所述降压型电路100以整流模式或降压模式工作，以及控制所述升压型电路200以升压模式或滤波模式工作，具体包括：确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；检测到所述第一电压采样值大于或等于母线电压对应的电压给定值，控制所述降压型电路100以所述降压模式工作，以及控制所述升压型电路200以所述滤波模式工作；检测到所述第一电压采样值小于所述母线电压对应的电压给定值，控制所述降压型电路100以所述整流模式工作，以及控制所述升压型电路200以所述滤波模式工作。
在该技术方案中，通过确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值，可以确定交流电压瞬时值，并且瞬时交流电压的绝对值小于直流母线电压给定时进入电压不控制模式，此时不需要进行降压处理，此时进入不控制模式有利于降低驱动电路功耗，否则进入降压控制模式，以及时降低交流电压，进而降低交流电压对降压型电路100后级电路的冲击。
其中，电压不控制模式下，降压型电路100工作于二极管整流或同步整流状态，升压型电路200工作于直通滤波状态。
在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路100以整流模式或降压模式工作，以及控制所述升压型电路200以升压模式或滤波模式工作，具体包括：确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，检测所述交流电压的瞬时值；检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述升压型电路200以所述升压模式工作，以及控制所述降压型电路100以所述整流模式工作；检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述降压型电路100以降压模式工作，以及控制所述升压型电路200以所述滤波模式工作。
在该技术方案中，第一电压采样值小于第二电压采样值，若检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，则继续预测检测交流电压升高的趋势，因此，继续检测所述交流电压的瞬时值。
进一步的，若检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述降压型电路100以降压模式工作，以及时降低交流电压，另外，通过控制所述升压型电路200以所述滤波模式工作，以提高驱动电路效率。
在上述任一技术方案中，进一步地，根据所述交流电压和所述母线电压，控制所述降压型电路100以整流模式或降压模式工作，以及控制所述升压型电路200以升压模式或滤波模式工作，具体包括：确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述升压型电路200以升压模式工作。
在该技术方案中，检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述升压型电路200以升压模式工作，也即通过及时升压来降低直流母线电压的跌落和电机停机的可能性。
其中，在升压模式下，降压型电路100工作于整流状态，同时，升压型电路200工作于升压调制状态。
在上述任一技术方案中，进一步地，所述电机为永磁式同步电机，所述驱动方 法还包括：确定所述永磁式同步电机的转速和反电动势系数；根据所述转速和所述反电动势系数确定所述母线电压对应的电压给定值。
在该技术方案中，通过反电动势系数确定母线电压对应的电压给定值，有利于进一步地提升对直流母线电压进行升降压调节的可靠性和灵活性。
其中，直流母线电压给定＝转速×相电压反电势系数×第三电压系数。
可选地，1≤第三电压系数≤2.5。
优选地，1.5≤第三电压系数≤2。
在上述任一技术方案中，进一步地，所述整流模式包括二极管整流模式和同步整流模式。
如图64所示，在本申请的第七方面的实施例，提供了一种空调器400，包括：电机402；如上述任一技术方案限定的升降压驱动电路404，驱动电路404被配置为控制电机402运行。
在该技术方案中，空调器包括如上述任一技术方案中的升降压驱动电路，因此，该空调器包括如上述任一技术方案中的升降压驱动电路的全部有益效果，因此不再赘述。
如图65所示，根据本申请第八方面的实施例，提供了一种计算机可读存储介质500，所述计算机可读存储介质500上存储有计算机程序，所述计算机程序被空调器400执行时实现上述任一项技术方案限定的驱动方法。
在本申请的描述中，术语“多个”指两个或两个以上，除非另有明确的限定。术语“上”、“下”等指示的方位或位置关系为基于附图的方位或位置关系，仅是为了便于描述本申请和简化描述，而不是指示或暗示所指的装置或元件必须具有特定的方位、以特定的方位构造和操作，因此不能理解为对本申请的限制。术语“安装”、“相连”、“连接”、“固定”等均应做广义理解，例如，“连接”可以是固定连接，也可以是可拆卸连接，或一体地连接；“相连”可以是直接相连，也可以通过中间媒介间接相连。对于本领域的普通技术人员而言，可以根据具体情况理解上述术语在本申请中的具体含义。
在本说明书的描述中，术语“一个实施例”、“一些实施例”、“具体实施例”等的描述意指结合该实施例或示例描述的具体特征、结构、材料或特点包含于本申请的至少一个实施例或示例中。在本说明书中，对上述术语的示意性表述不一定指的是相同的实施例或实例。而且，描述的具体特征、结构、材料或特点可以在任何的一个或多个实施例或示例中以合适的方式结合。
以上所述仅为本申请的优选实施例而已，并不用于限制本申请，对于本领域的技术人员来说，本申请可以有各种更改和变化。凡在本申请的精神和原则之内，所作的任何修改、等同替换、改进等，均应包含在本申请的保护范围之内。

Claims (59)

  1. 一种升降压驱动电路，其中，包括：
    升压型电路，所述升压型电路被配置为能够对供电信号进行功率因数校正处理或整流处理，
    降压型电路，所述降压型电路的输入端连接至所述升压型电路的输出端，所述降压型电路包括：
    第一功率管和第二功率管，依次串联于所述升压型电路的高压输出端和低压输出端之间，所述第二功率管的两端引出为高压母线和低压母线，
    其中，控制所述第一功率管和所述第二功率管交替导通，以对所述高压母线和所述低压母线之间的母线电压进行降压调制。
  2. 根据权利要求1所述的升降压驱动电路，其中，所述降压型电路包括：滤波电路，所述滤波电路与所述第二功率管并联连接，所述滤波电路用于对流经所述高压母线和所述低压母线的供电信号进行滤波处理。
  3. 根据权利要求2所述的升降压驱动电路，其中，所述滤波电路包括：
    第一感性元件，所述第一感性元件的第一端连接于所述第一功率管和所述第二功率管之间的公共端；
    第一容性元件，所述第一容性元件的第一端连接于所述第一感性元件的第二端，所述第一容性元件的第二端连接于所述低压母线。
  4. 根据权利要求1所述的升降压驱动电路，其中，所述升压型电路包括：
    第二感性元件，所述第二感性元件被配置为接入所述供电信号；
    桥式电路，所述桥式电路的任一桥臂中设有一个功率管，所述桥式电路的输入端连接至所述第二感性元件，所述桥式电路被配置为能够对所述供电信号进行整流处理或功率因数校正处理；
    第二容性元件，所述第二容性元件连接于所述桥式电路的两个输出端之间。
  5. 根据权利要求4所述的升降压驱动电路，其中，供电端被配置为向所述驱动电路输出供电信号，所述桥式电路包括：
    第三功率管、第四功率管、第五功率管和第六功率管，所述第三功率管与所述第四功率管之间的公共端连接至所述第二感性元件的第一端，所述供电端的第一输出端与所述第二感性元件的第二端相连，所述第五功率管与所述第六功率管之间的公共端连接至所述供电端的第二输出端，其中，所述第三功率管和所述第五功率管的公共端作为所述高压输出端，所述第四功率管和所述第六功率管的公共端作为所述低压输出端。
  6. 根据权利要求4所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以二极管整流模式工作，具体包括以下步骤：所述控制器控制所述桥式电路中的功率管均截止，所述反并联的第一二极管对所述供电信号进行整流。
  7. 根据权利要求5所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以同步整流模式工作，具体包括以下步骤：所述反并联的第一二极管导通时，所述控制器控制对应的功率管以第一占空比导通。
  8. 根据权利要求5所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以半同步整流模式工作，具体包括以下步骤：控制所述第三功率管和所述第五功率管截止，所述第四功率管的反并联的第一二极管导通时，所述控制器控制所述第四功率管导通，以及所述第六功率管的反并联的第一二极管导通时，所述控制器控制所述第六功率管导通。
  9. 根据权利要求5所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以半同步整流模式工作，具体包括以下步骤：控制所述第四功率管和所述第六功率管截止，所述第三功率管的反并联的第一二极管导通时，所述控制器控制所述第三功率管导通，以及所述第五功率管的反并联的第一二极管导通时，所述控制器控制所述第五功率管导通。
  10. 根据权利要求5所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以功率因数校正模式工作，具体包括以下步骤：
    所述供电信号向所述第三功率管和第四功率管之间的公共端流入时，所述第三功率管和所述第四功率管以第二占空比交替导通；
    所述第五功率管的反并联的第一二极管有电流流过时，所述控制器控制所述第五功率管以第三占空比导通，同时，所述控制器保持所述第六功率管截止；
    所述第六功率管的反并联的第一二极管有电流流过时，所述控制器控制所述第六功率管以所述第三占空比导通，同时，所述控制器保持所述第五功率管截止。
  11. 根据权利要求5所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以功率因数校正模式工作，具体包括以下步骤：
    所述供电信号向所述第五功率管和第六功率管之间的公共端流入时，所述第五功率管和所述第六功率管以第四占空比交替导通；
    所述第三功率管的反并联的第一二极管有电流流过时，所述控制器控制所述第三功率管以第五占空比导通，同时，所述控制器保持所述第四功率管截止；
    所述第四功率管的反并联的第一二极管有电流流过时，所述控制器控制所述第四功率管以所述第五占空比导通，同时，所述控制器保持所述第三功率管截止。
  12. 根据权利要求1所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至功率管的控制端，所述第二功率管设有反并联的第一二极管，
    所述控制器驱动所述降压型电路以滤波模式工作，具体包括以下步骤：所述控制器控制所述第一功率管导通，所述控制器控制所述第二功率管截止或与所述第一功率管交替导通，所述滤波电路对所述供电信号进行滤波处理。
  13. 根据权利要求1至10中任一项所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至功率管的控制端，
    所述控制器驱动所述降压型电路以降压模式工作，具体包括以下步骤：所述控制器控制所述第一功率管以第六占空比导通，同时，所述控制器控制所述第二功率管与所述第一功率管交替导通。
  14. 一种升降压驱动电路，其中，包括：
    图腾柱电路，所述图腾柱电路被配置为能够对供电信号进行功率因数校正处理或整流处理；
    降压型电路，所述降压型电路的输入端连接至所述图腾柱电路的输出端，所述降压型电路包括：
    第一功率管和第二功率管，依次串联于所述图腾柱电路的高压输出端和低压输出 端之间，所述第二功率管的两端引出为高压母线和低压母线，
    其中，所述降压型电路被配置为能够对所述供电信号进行降压处理或滤波处理。
  15. 根据权利要求14所述的升降压驱动电路，其中，所述降压型电路包括：滤波电路，所述滤波电路与所述第二功率管并联连接，所述滤波电路用于对流经所述高压母线和所述低压母线的供电信号进行滤波处理。
  16. 根据权利要求15所述的升降压驱动电路，其中，所述滤波电路包括：
    第一感性元件，所述第一感性元件的第一端连接于所述第一功率管和所述第二功率管之间的公共端；
    第一容性元件，所述第一容性元件的第一端连接于所述第一感性元件的第二端，所述第一容性元件的第二端连接于所述低压母线。
  17. 根据权利要求14所述的升降压驱动电路，其中，所述图腾柱电路包括：
    第二感性元件，所述第二感性元件被配置为接入所述供电信号；
    桥式电路，所述桥式电路的任一桥臂中设有一个功率管，所述桥式电路的输入端连接至所述第二感性元件，所述桥式电路被配置为能够对所述供电信号进行功率因数校正处理或整流处理；
    第二容性元件，所述第二容性元件连接于所述桥式电路的两个输出端之间。
  18. 根据权利要求17所述的升降压驱动电路，其中，供电端被配置为向所述驱动电路输出供电信号，所述桥式电路包括：
    第三功率管、第四功率管、第五功率管和第六功率管，所述第三功率管与所述第四功率管之间的公共端连接至所述第二感性元件的第一端，所述供电端的第一输出端与所述第二感性元件的第二端相连，所述第五功率管与所述第六功率管之间的公共端连接至所述供电端的第二输出端，其中，所述第三功率管和所述第五功率管的公共端作为所述高压输出端，所述第四功率管和所述第六功率管的公共端作为所述低压输出端。
  19. 根据权利要求17所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以二极管整流模式工作，具体包括以下步骤：所述控制器控制所述桥式电路中的功率管均截止，所述反并联的第一二极管对所述供电信号进行整流。
  20. 根据权利要求18所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以同步整流模式工作，具体包括以下步骤：所述反并联的第一二极管导通时，所述控制器控制对应的功率管以第一占空比导通。
  21. 根据权利要求18所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以半同步整流模式工作，具体包括以下步骤：控制所述第三功率管和所述第四功率管截止，所述第五功率管的反并联的第一二极管导通时，所述控制器控制所述第五功率管导通，以及所述第六功率管的反并联的第一二极管导通时，所述控制器控制所述第六功率管导通。
  22. 根据权利要求18所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以半同步整流模式工作，具体包括以下步骤：控制所述第五功率管和所述第六功率管截止，所述第三功率管的反并联的第一二极管导通时，所述控制器控制所述第三功率管导通，以及所述第四功率管的反并联的第一二极 管导通时，所述控制器控制所述第四功率管导通。
  23. 根据权利要求18所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以功率因数校正模式工作，具体包括以下步骤：
    所述供电信号向所述第三功率管和第四功率管之间的公共端流入时，所述第三功率管和所述第四功率管以第二占空比交替导通；
    所述第五功率管的反并联的第一二极管有电流流过时，所述控制器控制所述第五功率管以第三占空比导通，同时，所述控制器保持所述第六功率管截止；
    所述第六功率管的反并联的第一二极管有电流流过时，所述控制器控制所述第六功率管以所述第三占空比导通，同时，所述控制器保持所述第五功率管截止。
  24. 根据权利要求18所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述功率管均设有反并联的第一二极管，
    所述控制器驱动所述桥式电路以功率因数校正模式工作，具体包括以下步骤：
    所述供电信号向所述第五功率管和第六功率管之间的公共端流入时，所述第五功率管和所述第六功率管以第四占空比交替导通；
    所述第三功率管的反并联的第一二极管有电流流过时，所述控制器控制所述第三功率管以第五占空比导通，同时，所述控制器保持所述第四功率管截止；
    所述第四功率管的反并联的第一二极管有电流流过时，所述控制器控制所述第四功率管以上述第五占空比导通，同时，所述控制器保持所述第三功率管截止。
  25. 根据权利要求14所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至功率管的控制端，所述第二功率管设有反并联的第一二极管，
    所述控制器驱动所述降压型电路以滤波模式工作，具体包括以下步骤：所述控制器控制所述第一功率管导通，所述控制器控制所述第二功率管截止或与所述第一功率管交替导通，所述滤波电路对所述供电信号进行滤波处理。
  26. 根据权利要求14至23中任一项所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至功率管的控制端，
    所述控制器驱动所述降压型电路以降压模式工作，具体包括以下步骤：
    所述控制器控制所述第一功率管以第六占空比导通，同时，所述控制器控制所述第二功率管与所述第一功率管交替导通。
  27. 一种升降压驱动电路，其中，包括：
    降压型电路，所述降压型电路包括桥式电路，所述桥式电路的任一桥臂中设有一个半导体管，所述降压型电路被配置为接入供电端输入的供电信号；
    升压型电路，所述升压型电路的输入端连接至所述降压型电路的输出端，所述升压型电路被配置为能够升高所述供电信号；
    第七功率管，连接至所述桥式电路的两个输出端，且连接至所述升压型电路的两个输入端，所述第七功率管被配置为能够对所述升压型电路进行续流。
  28. 根据权利要求27所述的升降压驱动电路，其中，所述桥式电路包括：
    第一单向导通管、第八功率管、第二单向导通管和第九功率管，所述第一单向导通管与所述第八功率管之间的公共端连接至所述供电端的第一输出端，所述第二单向导通管与所述第九功率管之间的公共端连接至所述供电端的第二输出端，所述第一单向导通管和所述第二单向导通管的公共端作为所述桥式电路的高压输出端，所述第八功率管和所述第九功率管的公共端作为所述桥式电路的低压输出端，其中，所述第一单向导通管和第二单向导通管均截止，所述第七功率管对所述升压型电路进行续流。
  29. 根据权利要求28所述的升降压驱动电路，其中，还包括：控制器，所述控制 器连接至所述功率管的控制端，所述第八功率管设有反并联的第二二极管，所述第九功率管设有反并联的第三二极管，
    所述控制器驱动所述桥式电路以二极管整流模式工作，具体包括：所述控制器控制所述第八功率管和所述第九功率管均截止，所述第二二极管和所述第三二极管对所述供电信号进行整流，其中，所述第一单向导通管的漏极电压高于源极电压，所述第一单向导通管导通；所述第二单向导通管的漏极电压高于源极电压，所述第二单向导通管导通。
  30. 根据权利要求28所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第八功率管设有反并联的第二二极管，所述第九功率管设有反并联的第三二极管，
    所述控制器驱动所述桥式电路以同步整流模式工作，具体包括：所述第一单向导通管的漏极电压高于源极电压，所述第一单向导通管导通，同时，所述第九功率管导通，所述第二单向导通管的漏极电压高于源极电压，所述第二单向导通管导通，同时，所述第八功率管导通。
  31. 根据权利要求28所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第八功率管设有反并联的第二二极管，所述第九功率管设有反并联的第三二极管，
    所述控制器驱动所述桥式电路以二极管整流降压模式工作，具体包括：
    所述控制器控制所述第八功率管和所述第九功率管均截止，所述第二二极管和所述第三二极管对所述供电信号进行整流；
    所述第一单向导通管的漏极电压高于源极电压，所述控制器触发所述第一单向导通管按照第一占空比导通或截止，所述第二单向导通管的漏极电压高于源极电压，所述控制器触发所述第二单向导通管按照第二占空比导通或截止。
  32. 根据权利要求28所述的升降压驱动电路，其中，还包括：控制器，所述控制器连接至所述功率管的控制端，所述第八功率管设有反并联的第二二极管，所述第九功率管设有反并联的第三二极管，
    所述控制器驱动所述桥式电路以同步整流降压模式工作，具体包括：所述第一单向导通管的漏极电压高于源极电压，所述第九功率管导通，同时，所述控制器控制所述第一单向导通管按照第三占空比导通或截止，所述第二单向导通管的漏极电压高于源极电压，所述第八功率管导通，同时，所述控制器控制所述第二单向导通管按照第四占空比导通或截止。
  33. 根据权利要求28至32中任一项所述的升降压驱动电路，其中，还包括：
    所述第一单向导通管和所述第九功率管中的一个功率管为反向阻断开关管或绝缘栅门极晶体管，所述第一单向导通管和所述第九功率管中的另一个功率管为不控二极管或金属氧化物半导体管；以及
    所述第八功率管和所述第二单向导通管中的一个功率管为反向阻断开关管或绝缘栅门极晶体管，所述第八功率管和所述第二单向导通管中的另一个功率管为不控二极管或金属氧化物半导体管。
  34. 根据权利要求33所述的升降压驱动电路，其中，所述反向阻断开关管包括：
    第一N沟道金属氧化物半导体管和第二N沟道金属氧化物半导体管，两个所述N沟道金属氧化物半导体管的漏极相接；
    比较器，所述第一N沟道金属氧化物半导体管的源极连接至所述比较器的第一输入端，所述第二N沟道金属氧化物半导体管的源极连接至所述比较器的第二输入端；
    控制器，所述控制器的输入端连接至所述比较器的输出端，所述控制器的输出端 连接至N沟道金属氧化物半导体管的栅极。
  35. 根据权利要求33所述的升降压驱动电路，其中，所述反向阻断开关管包括：
    第一P沟道金属氧化物半导体管和第二P沟道金属氧化物半导体管，两个所述P沟道金属氧化物半导体管的源极相接；
    比较器，所述第一P沟道金属氧化物半导体管的漏极连接至所述比较器的第一输入端，所述第二P沟道金属氧化物半导体管的漏极连接至所述比较器的第二输入端；
    控制器，所述控制器的输入端连接至所述比较器的输出端，所述控制器的输出端连接至P沟道金属氧化物半导体管的栅极。
  36. 根据权利要求33所述的升降压驱动电路，其中，所述反向阻断开关管包括：串联的二极管和金属氧化物半导体管，所述金属氧化物半导体管设有反并联的二极管，所述二极管的导通方向与所述反并联的二极管的导通方向相反。
  37. 根据权利要求27至32中任一项所述的升降压驱动电路，其中，所述升压型电路包括：
    第三感性元件，所述第三感性元件的第一端连接至所述桥式电路的高压输出端；
    第十功率管，连接于所述第三感性元件的第二端与所述桥式电路的低压输出端之间；
    第十一功率管，连接于所述第三感性元件的第二端与第三容性元件的第一端之间，所述第三容性元件的第二端连接至所述低压输出端，
    控制器，所述控制器连接至所述第十功率管的控制端和所述第十一功率管的控制端，
    所述控制器控制所述升压型电路以升压模式运行，具体包括：所述控制器根据所述高压输出端和所述低压输出端之间的母线电压对应的电压给定值和所述母线电压确定第五占空比，所述控制器按照所述第五占空比控制所述第十功率管导通或截止，第十一功率管与所述第十功率管交替导通或保持截止。
  38. 根据权利要求27至32中任一项所述的升降压驱动电路，其中，所述升压型电路包括：
    第三感性元件，所述第三感性元件的第一端连接至所述桥式电路的高压输出端；
    第十功率管，连接于所述第三感性元件的第二端与所述桥式电路的低压输出端之间；
    第十一功率管，连接于所述第三感性元件的第二端与第三容性元件的第一端之间，所述第三容性元件的第二端连接至所述低压输出端，
    控制器，所述控制器连接至所述第十功率管的控制端和所述第十一功率管的控制端，
    所述控制器控制所述升压型电路以滤波模式运行，具体包括：
    所述控制器控制所述第十一功率管导通，所述控制器控制所述第十功率管截止。
  39. 一种升降压驱动方法，其中，适用于如权利要求1至13中任一项所述的升降压驱动电路，所述驱动电路包括电连接的升压型电路和降压型电路，所述驱动方法包括：
    确定输入至所述驱动电路的交流电压，以及所述驱动电路的母线电压；
    根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作。
  40. 根据权利要求39所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，具体包括：
    确定母线电压对应的电压给定值；
    比较所述电压给定值与所述交流电压之间的大小关系；
    根据所述电压给定值与所述交流电压之间的大小关系，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作。
  41. 根据权利要求39所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，具体包括：
    确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；
    检测到所述第一电压采样值大于或等于母线电压对应的电压给定值，检测所述交流电压的瞬时值；
    检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述升压型电路以整流模式工作，控制所述降压型电路以滤波模式工作；
    检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述升压型电路以整流模式工作，控制所述降压型电路以降压模式工作。
  42. 根据权利要求39所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，具体包括：
    确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；
    确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；
    检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，检测所述交流电压的瞬时值；
    检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述升压型电路以功率因数校正模式工作，控制所述降压型电路以滤波模式工作；
    检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述升压型电路以整流模式工作，控制所述降压型电路以降压模式工作。
  43. 根据权利要求39所述的升降压驱动方法，其中，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述升压型电路以功率因数校正模式或整流模式工作，具体包括：
    确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；
    检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述升压型电路以功率因数校正模式工作。
  44. 根据权利要求39至43中任一项所述的升降压驱动方法，其中，电机为永磁式同步电机，所述驱动方法还包括：
    确定所述永磁式同步电机的转速和反电动势系数；
    根据所述转速和所述反电动势系数确定所述母线电压对应的电压给定值。
  45. 一种升降压驱动方法，其中，适用于如权利要求14至26中任一项所述的驱动电路，所述驱动电路包括电连接的图腾柱电路和降压型电路，所述驱动方法包括：
    确定输入至所述驱动电路的交流电压，以及所述驱动电路的母线电压；
    根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作。
  46. 根据权利要求45所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，具体包括：
    确定母线电压对应的电压给定值；
    比较所述电压给定值与所述交流电压之间的大小关系；
    根据所述电压给定值与所述交流电压之间的大小关系，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作。
  47. 根据权利要求45所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，具体包括：
    确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；
    检测到所述第一电压采样值大于或等于母线电压对应的电压给定值，检测所述交流电压的瞬时值；
    检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述图腾柱电路以整流模式工作，控制所述降压型电路以滤波模式工作；
    检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述图腾柱电路以整流模式工作，控制所述降压型电路以降压模式工作。
  48. 根据权利要求45所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，具体包括：
    确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；
    确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；
    检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，检测所述交流电压的瞬时值；
    检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述图腾柱电路以功率因数校正模式工作，控制所述降压型电路以滤波模式工作；
    检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述图腾柱电路以整流模式工作，控制所述降压型电路以降压模式工作。
  49. 根据权利要求45所述的升降压驱动方法，其中，控制所述降压型电路以滤波模式或降压模式工作，以及控制所述图腾柱电路以功率因数校正模式或整流模式工作，具体包括：
    确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；
    检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述图腾柱电路以功率因数校正模式工作，同时，控制所述降压型电路以滤波模式工作。
  50. 根据权利要求45至49中任一项所述的升降压驱动方法，其中，电机为永磁式同步电机，所述驱动方法还包括：
    确定所述永磁式同步电机的转速和反电动势系数；
    根据所述转速和所述反电动势系数确定所述母线电压对应的电压给定值。
  51. 一种升降压驱动方法，其中，适用于如权利要求27至38中任一项所述的升降压驱动电路，所述驱动电路包括电连接的升压型电路和降压型电路，所述驱动方法包括：
    确定输入至所述驱动电路的交流电压，以及所述驱动电路的母线电压；
    根据所述交流电压和所述母线电压，控制所述降压型电路以整流模式或降压模式工作，以及控制所述升压型电路以升压模式或滤波模式工作。
  52. 根据权利要求51所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以整流模式或降压模式工作，以及控制所述升压型电路以升压模式或滤波模式工作，具体包括：
    确定母线电压对应的电压给定值；
    比较所述电压给定值与所述交流电压之间的大小关系；
    根据所述电压给定值与所述交流电压之间的大小关系，控制所述降压型电路以整流模式或降压模式工作，以及控制所述升压型电路以升压模式或滤波模式工作。
  53. 根据权利要求52所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以整流模式或降压模式工作，以及控制所述升压型电路以升压模式或滤波模式工作，具体包括：
    确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；
    检测到所述第一电压采样值大于或等于所述母线电压对应的电压给定值，控制所述降压型电路以所述降压模式工作，以及控制所述升压型电路以所述滤波模式工作；
    检测到所述第一电压采样值小于所述母线电压对应的电压给定值，控制所述降压型电路以所述整流模式工作，以及控制所述升压型电路以所述滤波模式工作。
  54. 根据权利要求52所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以整流模式或降压模式工作，以及控制所述升压型电路以升压模式或滤波模式工作，具体包括：
    确定所述交流电压的有效值与第一电压系数之间的乘积，并将乘积记作第一电压采样值；
    确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；
    检测到所述第一电压采样值小于所述母线电压对应的电压给定值，且检测到所述第二电压采样值大于或等于所述母线电压对应的电压给定值，检测所述交流电压的瞬时值；
    检测到所述交流电压的瞬时值小于所述母线电压对应的电压给定值，控制所述升压型电路以所述升压模式工作，以及控制所述降压型电路以所述整流模式工作；
    检测到所述交流电压的瞬时值大于或等于所述母线电压对应的电压给定值，控制所述降压型电路以降压模式工作，以及控制所述升压型电路以所述滤波模式工作。
  55. 根据权利要求52所述的升降压驱动方法，其中，根据所述交流电压和所述母线电压，控制所述降压型电路以整流模式或降压模式工作，以及控制所述升压型电路以升压模式或滤波模式工作，具体包括：
    确定所述交流电压的有效值与第二电压系数之间的乘积，并将乘积记作第二电压采样值；
    检测到所述第二电压采样值小于所述母线电压对应的电压给定值，控制所述升压 型电路以升压模式工作，同时，控制所述降压型电路以整流模式工作。
  56. 根据权利要求51至55中任一项所述的升降压驱动方法，其中，电机为永磁式同步电机，所述驱动方法还包括：
    确定所述永磁式同步电机的转速和反电动势系数；
    根据所述转速和所述反电动势系数确定所述母线电压对应的电压给定值。
  57. 根据权利要求51至55中任一项所述的升降压驱动方法，其中，
    所述整流模式包括二极管整流模式和同步整流模式。
  58. 一种空调器，其中，包括：
    电机；
    如权利要求1至38中任一项所述的升降压驱动电路，所述驱动电路被配置为控制所述电机运行。
  59. 一种计算机可读存储介质，其中，所述计算机可读存储介质上存储有计算机程序，所述计算机程序被执行时实现如权利要求39至57中任一项所述的升降压驱动方法。
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