WO2021128109A1 - 无线通信装置及信号处理方法 - Google Patents

无线通信装置及信号处理方法 Download PDF

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Publication number
WO2021128109A1
WO2021128109A1 PCT/CN2019/128483 CN2019128483W WO2021128109A1 WO 2021128109 A1 WO2021128109 A1 WO 2021128109A1 CN 2019128483 W CN2019128483 W CN 2019128483W WO 2021128109 A1 WO2021128109 A1 WO 2021128109A1
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Prior art keywords
carrier
signal
frequency band
frequency
communication device
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PCT/CN2019/128483
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English (en)
French (fr)
Inventor
高鹏
易岷
梁建
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华为技术有限公司
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Priority to CN201980103237.3A priority Critical patent/CN114846776B/zh
Priority to PCT/CN2019/128483 priority patent/WO2021128109A1/zh
Publication of WO2021128109A1 publication Critical patent/WO2021128109A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits

Definitions

  • This application relates to the field of communication technology, and in particular to wireless communication devices and signal processing methods.
  • CA Carrier aggregation
  • the embodiments of the present application provide a wireless communication device and a signal processing method for processing signals carried on multiple discontinuous carriers, which helps reduce the design complexity of the wireless communication device and save hardware resources.
  • a wireless communication device including: a radio frequency front-end channel for receiving broadband radio frequency signals, and the broadband radio frequency signals include discontinuous signal frequency components of a first carrier and a second carrier.
  • the local oscillator circuit is used to generate the local oscillator signal.
  • the mixer circuit coupled with the radio frequency front-end channel and the local oscillator circuit is used to down-convert the broadband radio frequency signal according to the local oscillator signal to obtain a baseband signal.
  • the filter coupled with the mixer circuit is used for filtering the baseband signal to obtain a filtered signal.
  • the bandwidth of the filtered signal includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundancy bandwidth between the first carrier and the second carrier.
  • a wireless communication device including:
  • the mixing circuit is used to receive a broadband radio frequency signal and a local oscillator signal, and perform a down-conversion operation on the broadband radio frequency signal according to the local oscillator signal to obtain a baseband signal, wherein the broadband radio frequency signal contains a discontinuous first carrier And the signal frequency component of the second carrier;
  • the filter is used to perform a filtering operation on the baseband signal to obtain a filtered signal.
  • the bandwidth of the filtered signal includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and between the first carrier and the Redundant bandwidth between the second carriers.
  • the RF front-end channel is optional, and the local oscillator circuit is also optional.
  • the broadband radio frequency signal whose bandwidth includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundant bandwidth between the first carrier and the second carrier, is subjected to down-conversion operation and After the filtering operation, the bandwidth of the obtained signal still includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundant bandwidth between the first carrier and the second carrier.
  • the above-mentioned wideband radio frequency signal is described with respect to the radio frequency signal of a single carrier, and the description is unified here.
  • the first carrier and the second carrier are two component carriers of the discontinuous carrier aggregation of the long-term evolution system. This helps reduce the design complexity of the wireless communication device in the long-term evolution system and saves hardware resources in the long-term evolution system.
  • the first carrier and the second carrier are two component carriers of the non-contiguous carrier aggregation of the new radio system. This helps reduce the design complexity of the wireless communication device in the new radio system and saves hardware resources in the new radio system.
  • the first carrier and the second carrier belong to the millimeter wave frequency band.
  • the technical solutions provided by the embodiments of the present application may be applicable to the millimeter wave frequency band. Of course it is not limited to this.
  • the first carrier and the second carrier are in the same frequency band. This helps to reduce the requirement for the working bandwidth of the filter, thereby helping to save the power consumption of the filter, thereby saving the overall power consumption of the wireless communication device.
  • the first carrier is the carrier of the long-term evolution system
  • the second carrier is the carrier of the new radio system
  • the first carrier and the second carrier are dual-connected two carriers. That is to say, the technical solutions provided by the embodiments of the present application can be applied to the dual-connection working mode.
  • the frequency band where the first carrier is located is the same as the frequency band where the second carrier is located. This helps to reduce the requirement for the working bandwidth of the filter, thereby helping to save the power consumption of the filter, thereby saving the overall power consumption of the wireless communication device.
  • the frequency band where the first carrier is located includes frequency band 3
  • the frequency band where the second carrier is located includes frequency band n3.
  • the frequency band where the first carrier is located includes frequency band 41
  • the frequency band where the second carrier is located includes frequency band n41.
  • the frequency band where the first carrier is located is different from the frequency band where the second carrier is located, but there is overlap. This helps to reduce the requirement for the working bandwidth of the filter, thereby helping to save the power consumption of the filter, thereby saving the overall power consumption of the wireless communication device.
  • the frequency band where the first carrier is located is different from the frequency band where the second carrier is located, but the frequency band where the first carrier is located completely covers the frequency band where the second carrier is located, or the frequency band where the second carrier is located completely covers the frequency band where the second carrier is located.
  • the frequency band of a carrier includes frequency band 42, and the frequency band where the second carrier is located includes frequency band n77.
  • the frequency band where the first carrier is located includes frequency band 42, and the frequency band where the second carrier is located includes frequency band n78.
  • the frequency of the local oscillator signal is the middle frequency between the highest center frequency and the lowest center frequency of the carrier included in the broadband radio frequency signal.
  • the frequency of the local oscillator signal is the middle frequency of the broadband radio frequency signal.
  • the wireless communication device further includes: an analog-to-digital converter coupled with the filter for performing analog-to-digital conversion operations on the filtered signal, wherein the working bandwidth of the analog-to-digital converter is greater than or equal to the The bandwidth of the filtered signal.
  • an analog-to-digital converter coupled with the filter for performing analog-to-digital conversion operations on the filtered signal, wherein the working bandwidth of the analog-to-digital converter is greater than or equal to the The bandwidth of the filtered signal.
  • the wireless communication device further includes a carrier separator, which is used to separate the digital signal obtained after the analog-to-digital conversion operation to obtain the signal of the first carrier and the signal of the second carrier.
  • a carrier separator which is used to separate the digital signal obtained after the analog-to-digital conversion operation to obtain the signal of the first carrier and the signal of the second carrier.
  • the local oscillator circuit and the mixer circuit are integrated in the radio frequency chip, and the carrier separator is integrated in the baseband chip.
  • the wireless communication device is integrated in the radio frequency chip.
  • the wireless communication device is a terminal or a base station.
  • the broadband radio frequency signal may also include three or more non-continuous signals.
  • the signal frequency component of the carrier Based on this, the design principle of the wireless communication device can be inferred based on the technical solution described above, and will not be repeated here.
  • a signal processing method is provided, which is applied to a wireless communication device.
  • the method includes: receiving a broadband radio frequency signal, the broadband radio frequency signal contains discontinuous signal frequency components of a first carrier and a second carrier; and generating a local oscillator Signal; according to the local oscillator signal, the broadband radio frequency signal is down-converted to obtain a baseband signal; the baseband signal is filtered to obtain a filtered signal; the bandwidth of the filtered signal includes the signal bandwidth of the first carrier, The signal bandwidth of the two carriers, and the redundant bandwidth between the first carrier and the second carrier.
  • the method further includes: performing an analog-to-digital conversion operation on the filtered signal, wherein the working bandwidth of the analog-to-digital converter used when performing the analog-to-digital conversion operation is greater than or equal to that of the filtered signal bandwidth.
  • the method further includes: separating the digital signal obtained after the analog-to-digital conversion operation to obtain the signal of the first carrier and the signal of the second carrier.
  • a signal processing device which is used to execute any of the signal processing methods provided in the second aspect or the second aspect.
  • the signal processing device may be the above-mentioned wireless communication device, or a chip, or a terminal or a network device (such as a base station).
  • the device includes various modules for executing the second aspect or the method provided by any one of the possible designs of the second aspect.
  • the device includes a memory and a processor, the memory is used to store a computer program, and the processor is used to call the computer program to execute the second aspect or any one of the possible designs provided in the second aspect.
  • a computer-readable storage medium on which a computer program is stored, and when the computer program is called by a computer, the computer is caused to execute the method provided in the second aspect or any one of its possible designs.
  • a computer program product which when running on a computer, enables the method provided in the second aspect or any one of its possible designs to be executed.
  • any of the signal processing methods, signal processing devices, computer-readable storage media, or computer program products provided above are all used to execute the corresponding wireless communication devices provided above, and therefore, what they can achieve For the beneficial effects, please refer to the beneficial effects in the corresponding wireless communication device, which will not be repeated here.
  • FIG. 1A is a schematic diagram of a communication system applicable to embodiments of the present application.
  • FIG. 1B is a schematic diagram of another communication system applicable to the embodiments of the present application.
  • FIG. 2 is a schematic diagram of the hardware structure of a communication device applicable to an embodiment of the present application
  • FIG. 3 is a schematic diagram of a frequency spectrum in an NC-CA working mode applicable to an embodiment of the present application
  • 4A is a schematic diagram of a frequency spectrum in a discontinuous EN-DC operating mode in a frequency band applicable to embodiments of the present application;
  • 4B is a schematic diagram of a frequency spectrum in a non-continuous EN-DC working mode between frequency bands applicable to an embodiment of the present application;
  • FIG. 4C is a schematic diagram of a frequency spectrum in another non-continuous inter-band EN-DC operating mode applicable to an embodiment of the present application.
  • FIG. 5 is a schematic structural diagram of a wireless communication device provided by an embodiment of this application.
  • FIG. 6 is a schematic structural diagram of another wireless communication device provided by an embodiment of this application.
  • FIG. 7 is a schematic diagram of the frequency spectrum of the signals of each node in the working process of the wireless communication device shown in FIG. 6 according to an embodiment of the application;
  • FIG. 8 is a schematic structural diagram of another wireless communication device provided by an embodiment of this application.
  • FIG. 9 is a schematic diagram of the frequency spectrum of the signals of each node in the working process of the wireless communication device shown in FIG. 8 according to an embodiment of the application;
  • FIG. 10 is a schematic diagram of the working bandwidth of a filter and an analog-to-digital converter according to an embodiment of the application;
  • FIG. 11 is a schematic diagram of the working bandwidth of another filter and analog-to-digital converter provided by an embodiment of the application.
  • FIG. 12 is a schematic structural diagram of a carrier separator provided by an embodiment of the application.
  • FIG. 13 is a schematic diagram of the frequency spectrum of the signal of each node in the working process of the carrier separator in FIG. 12 according to an embodiment of the application;
  • FIG. 14 is a schematic structural diagram of another carrier separator provided by an embodiment of this application.
  • FIG. 15 is a schematic flowchart of a signal processing method provided by an embodiment of this application.
  • the technical solutions provided by the embodiments of this application can be applied to various communication systems, for example, the fifth generation (5G) mobile communication systems such as 5G NR systems, future evolution systems, or multiple communication convergence systems, etc. Used in existing communication systems such as LTE communication systems.
  • the application scenarios of the technical solution provided by this application can include multiple, such as machine to machine (M2M), macro and micro communications, enhanced mobile broadband (eMBB), ultra-high reliability and ultra-low Scenarios such as ultra-reliable & low latency communication (uRLLC) and massive machine type communication (mMTC).
  • M2M machine to machine
  • eMBB enhanced mobile broadband
  • uRLLC ultra-reliable & low latency communication
  • mMTC massive machine type communication
  • These scenarios may include, but are not limited to, a communication scenario between a terminal and a terminal, a communication scenario between a network device and a network device, a communication scenario between a network device and a terminal, and so on.
  • the communication system includes one or more network devices 10 (only one is shown) and one or more terminals connected to each network device 10 20.
  • FIG. 1B is a schematic diagram of a communication system applicable to another embodiment of the present application.
  • the communication system includes one or more network devices 10 and one or more terminals 20. Among them, one terminal 20 can be connected to multiple network devices 10. Different network devices among the multiple network devices 10 may support different communication standards. For example, as shown in FIG. 1B, one of the network devices 10 is an LTE base station, and the other network device 10 is an NR base station.
  • FIG. 1A and FIG. 1B are only schematic diagrams, and do not constitute a limitation on the application scenarios of the technical solutions provided in this application.
  • the network device 10 may be a transmission reception point (TRP), a base station, a relay station, or an access point.
  • the network device 10 may be a network device in a 5G communication system or a network device in a future evolution network; it may also be a wearable device or a vehicle-mounted device. It can also be the base transceiver station (BTS) in the global system for mobile communication (GSM) or code division multiple access (CDMA) network, or broadband
  • the NB (NodeB) in wideband code division multiple access (WCDMA) may also be the eNB or eNodeB (evolutional NodeB) in long term evolution (LTE).
  • the network device 10 may also be a wireless controller in a cloud radio access network (cloud radio access network, CRAN) scenario.
  • cloud radio access network cloud radio access network, CRAN
  • the terminal 20 may be a user equipment (UE), an access terminal, a UE unit, a UE station, a mobile station, a mobile station, a remote station, a remote terminal, a mobile device, a UE terminal, a wireless communication device, a UE agent, or a UE device Wait.
  • the access terminal can be a cellular phone, a cordless phone, a session initiation protocol (SIP) phone, a wireless local loop (WLL) station, a personal digital assistant (PDA), with wireless communication Functional handheld devices, computing devices or other processing devices connected to wireless modems, in-vehicle devices, wearable devices, terminals in 5G networks or terminals in the future evolution of public land mobile network (PLMN) networks, etc. .
  • each network element (for example, the network device 10 and the terminal 20, etc.) in FIG. 1A and FIG. 1B may be implemented by the communication device 200 in FIG. 2.
  • Fig. 2 is a schematic diagram of the hardware structure of a communication device applicable to an embodiment of the present application.
  • the communication device 200 may include a 201 part and a 202 part.
  • the 201 part is mainly used for the transmission and reception of radio frequency signals and the conversion of radio frequency signals and baseband signals.
  • Part 202 is mainly used for baseband signal processing and control of the communication device 20.
  • the part 201 can generally be called a transceiver unit, transceiver, transceiver circuit, or transceiver.
  • Part 202 is usually the control center of the communication device 200, and may generally be referred to as a processing unit.
  • Part 201 may include an antenna 2011 and a radio frequency unit 2012.
  • the radio frequency unit 2012 is mainly used for radio frequency processing.
  • the device for implementing the receiving function in part 201 can be regarded as the receiving unit, and the device for implementing the sending function as the sending unit, that is, the part 201 includes the receiving unit and the sending unit.
  • the receiving unit may also be called a receiver, a receiver, or a receiving circuit, and the sending unit may be called a transmitter, a transmitter, or a transmitting circuit, etc.
  • Part 202 may include one or more single boards, and each single board may include one or more processors 2021 and one or more memories 2022.
  • the processor 2021 is configured to read and execute programs in the memory 2022 to implement baseband processing functions and control the communication device 200. If there are multiple boards, each board can be interconnected to increase processing capacity. As an optional implementation, multiple boards may share one or more processors 2021, or multiple boards may share one or more memories 2022, or multiple boards may share one or more processors at the same time.
  • a processor 2021 may share one or more processors 2021, or multiple boards may share one or more memories 2022, or multiple boards may share one or more processors at the same time.
  • the radio frequency unit 2012 may include a radio frequency chip.
  • Part 202 may include a baseband chip.
  • the aforementioned communication device 200 may be a general-purpose device or a special-purpose device.
  • the embodiment of the present application does not limit the type of the communication device 200.
  • the carrier is a radio wave of a specific frequency.
  • the carrier may be called a carrier component (CC).
  • the signal spectrum of the baseband signal is located near or close to the zero point, and can also be called a "low frequency signal”.
  • Broadband radio frequency signals are relative to radio frequency signals that contain the signal frequency component of a carrier wave.
  • the broadband radio frequency signal may be an intermediate frequency signal.
  • the broadband radio frequency signal can be a high frequency signal.
  • non-contiguous carrier aggregation intra-band non-contiguous carrier aggregation, NC-CA
  • the NC-CA working mode is defined in both the LTE protocol and the NR protocol.
  • a discontinuous carrier aggregation signal is defined.
  • frequency band A contains two carriers (labeled as CC1 and CC2, respectively).
  • the bandwidths of these two carriers are BW CC1 and BW CC2 , and the center frequencies are f CC1 and f, respectively.
  • CC2 , and f CC2 >f CC1 then when At this time, the carriers CC1 and CC2, and the redundant frequency components between the two carriers are defined as discontinuous carrier aggregation signals.
  • Figure 3 illustrates the frequency domain resources occupied by the discontinuous carrier aggregation signals.
  • Fig. 3 is an example of non-contiguous carrier aggregation of 2 carriers for illustration. In practical applications, there may be discontinuous carrier aggregation of more than two carriers. In this case, the two or more carriers and the redundant frequency components between the two or more carriers are defined as discontinuous carrier aggregation signals.
  • 4G-5G dual connectivity E-UTRA/NR dual connectivity, EN-DC
  • the EN-DC working mode is specifically defined, that is, the terminal can connect to the NR base station and the LTE base station at the same time, and perform both at the same time.
  • the communication of this standard is shown in Figure 1B.
  • the terminal In the EN-DC working mode, the terminal needs to maintain communication with the LTE base station and the NR base station, that is, it needs to receive the LTE standard radio frequency signal issued by the LTE base station and the NR standard radio frequency signal issued by the NR base station.
  • the radio frequency signals of these two communication standards are allocated in the operating frequency bands of their respective systems.
  • the concept of the EN-DC signal is similar to the concept of the above-mentioned discontinuous carrier aggregation signal.
  • the difference between the two is that the carriers involved in the discontinuous carrier aggregation signal are all carriers under the same communication standard, such as all LTE carriers or all NR carriers, while some of the carriers involved in EN-DC are LTE carriers , Some of the carriers are NR carriers.
  • the LTE carrier is the carrier called by the LTE base station
  • the NR carrier is the carrier called by the NR base station.
  • LTE signals that is, signals sent by LTE base stations
  • NR signals that is, signals sent by NR base stations
  • Application scenario 1 The LTE signal and the NR signal are allocated in the corresponding frequency band, that is, the network device can schedule the terminal according to the EN-DC operating mode in the frequency band.
  • the frequency bands of the NR system and the LTE system are numbered the same, and the frequency coverage is the same.
  • the uplink operating frequency range of E-UTRA band 1 is 1920MHz (megahertz) ⁇ 1980MHz, and the downlink operating frequency range is 2110MHz ⁇ 2170MHz;
  • the uplink operating frequency range of NR band n1 is 1920MHz ⁇ 1980MHz, the downlink operating frequency range is 2110MHz ⁇ 2170MHz.
  • the NR system has a similar relationship with other frequency bands with the same number in the LTE system.
  • the frequency bands with the same number in the NR system and the LTE system are referred to as "corresponding frequency bands”.
  • the operating mode is defined as the intra-band non-contiguous EN-DC (intra-band non-contiguous EN-DC) operating mode .
  • the frequency spectrum diagram in the discontinuous EN-DC operating mode in the frequency band is shown in Figure 4A.
  • the network device calls an LTE carrier (labeled LTE CC) and an NR carrier (labeled NR CC).
  • LTE CC is allocated in E-UTRA frequency band X, with a bandwidth of BW LTE_CC and a center frequency of f LTE_CC .
  • NR CC is allocated in the NR frequency band nX, with a bandwidth of BW NR_CC and a center frequency of f NR_CC .
  • the frequency ranges of the E-UTRA band X and the NR band nX are the same.
  • EN-DC operating mode is defined as an inter-band EN-DC (inter-band EN-DC) operating mode.
  • the LTE carrier is allocated in the E-UTRA frequency band X
  • the NR carrier is allocated in the NR frequency band nY
  • X and Y are not equal, and there is no overlap between the frequency band X and the frequency band nY, as shown in Figure 4B Show.
  • LTE CC is allocated in E-UTRA frequency band X, with a bandwidth of BW LTE_CC and a center frequency of f LTE_CC .
  • NR CC is allocated in the NR band nY, with a bandwidth of BW NR_CC and a center frequency of f NR_CC . There is no overlap between the frequency ranges of E-UTRA band X and NR band nX.
  • the LTE carrier is allocated in the E-UTRA frequency band X
  • the NR carrier is allocated in the NR frequency band nY.
  • X and Y are not equal, but there is overlap between the frequency band X and the frequency band nY.
  • the LTE carrier and the NR carrier are allocated to different coded frequency bands, but their frequency spectrums overlap, or the frequency spectrums are close to (or close to) each other.
  • one of the two frequency bands may partially cover the other frequency band.
  • one of the two frequency bands can completely cover the other frequency band.
  • the uplink and downlink frequency range of E-UTRA band 42 in the LTE system is 3400MHz ⁇ 3600MHz
  • the uplink and downlink frequency of NR band n78 in the NR system The coverage range is from 3300MHz to 3800MHz.
  • the NR band n78 can completely cover the E-UTRA band 42, as shown in Figure 4C.
  • the LTE CC is allocated in the E-UTRA frequency band 42, with a bandwidth of BW LTE_CC and a center frequency of f LTE_CC .
  • NR CC is allocated in the NR band n78 , with a bandwidth of BW NR_CC and a center frequency of f NR_CC .
  • the zero-IF architecture usually moves the signal from the radio frequency carrier frequency to the baseband through a frequency conversion process.
  • the superheterodyne structure usually moves the signal from the radio frequency carrier frequency to the baseband through two frequency conversion processing.
  • the NR system introduces the millimeter wave frequency band, that is, the NR FR2 (frequency range 2) frequency band defined in the NR communication standard.
  • NR FR2 is 24.25GHz ⁇ 52.60GHz.
  • NCA intra-band discontinuous carrier aggregation
  • Wireless communication devices working in the NR FR2 frequency band usually adopt a superheterodyne architecture.
  • the application scenario of the wireless communication device of the superheterodyne architecture is not limited to this.
  • At least one (species) in the embodiments of the present application includes one (species) or more (species).
  • Multiple (species) means two (species) or more than two (species).
  • at least one of A, B, and C includes: A alone, B alone, A and B simultaneously, A and C simultaneously, B and C simultaneously, and A, B, and C simultaneously.
  • A/B can mean A or B; the "and/or” in this document is only an association relationship describing associated objects, meaning that There are three relationships, such as A and/or B, which can mean: A alone exists, A and B exist at the same time, and B exists alone.
  • words such as “first” and “second” are used in the embodiments of the present application to distinguish the same or similar items that have basically the same function and effect.
  • words “first”, “second” and the like do not limit the quantity and execution order, and the words “first” and “second” do not limit the difference.
  • the wireless communication device 1 may include:
  • the radio frequency front-end channel 101 is used to receive a broadband radio frequency signal, and the broadband radio frequency signal contains non-continuous signal frequency components of the first carrier and the second carrier.
  • the bandwidth of the broadband radio frequency signal includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundancy bandwidth between the first carrier and the second carrier.
  • the RF front-end channel 101 can also be used to process broadband RF signals.
  • the processing specifically means that the signal enters the mixing circuit 103 (the mixing circuit used to obtain the baseband signal). Processing. For example, one or more of filtering operation, amplifying operation, high frequency mixing operation, or phase shifting operation is performed on the broadband radio frequency signal.
  • the devices/modules included in the RF front-end channel 101 are modules that perform these processing operations.
  • the devices/modules included in the radio frequency front-end channel 101 are different. For specific examples, refer to FIG. 6 or FIG. 8, etc.
  • the local oscillator circuit 102 is used to generate a local oscillator signal.
  • the local oscillator circuit 102 may include a phase locked loop.
  • the mixer circuit 103 coupled with the radio frequency front-end channel 101 and the local oscillator circuit 102 is used to perform a down-conversion operation on the broadband radio frequency signal according to the local oscillator signal to obtain a baseband signal.
  • the signal frequency component of the first carrier and the signal frequency component of the second carrier contained in the baseband signal change, but the signal bandwidth of the first carrier and the signal bandwidth of the second carrier may not change. That is, the bandwidth of the baseband signal includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundant bandwidth between the first carrier and the second carrier.
  • the filter 104 coupled with the mixer circuit 103 is used to perform a filtering operation on the baseband signal to obtain a filtered signal.
  • the bandwidth of the filtered signal includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundancy bandwidth between the first carrier and the second carrier.
  • the filtering operation helps to reduce the deterioration of the signal-to-noise ratio of the useful signal due to the aliasing characteristics when the subsequent analog-to-digital conversion operation is performed.
  • the filter 104 can also be used to adjust the amplitude of the signal so that the intensity of the output signal reaches a preset intensity.
  • the wireless communication device is for broadband radio frequency signals whose bandwidth includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundant bandwidth between the first carrier and the second carrier.
  • the bandwidth of the obtained signal still includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundant bandwidth between the first carrier and the second carrier.
  • a signal whose bandwidth contains the signal bandwidth of the first carrier and a signal whose bandwidth contains the signal bandwidth of the second carrier are respectively obtained.
  • the local oscillator circuit needs to generate at least one local oscillator signal based on the frequency of the first carrier and another local oscillator signal based on the frequency of the second carrier.
  • the filtering operation the baseband signals obtained based on the two local oscillator signals need to be filtered respectively.
  • the wireless communication device provided by the embodiment of the present application helps to reduce the number of local oscillator signals, where different local oscillator signals have different frequencies, and helps reduce the number of executions of filtering operations. This helps to reduce the design complexity of the wireless communication device.
  • it helps to reduce the number of local oscillator circuits used to generate local oscillator signals and the number of filters used to perform filtering operations, thereby helping to save hardware resources.
  • the wireless communication device 1 further includes: an analog-to-digital converter 105 coupled with the filter 104 for performing analog-to-digital conversion operations on the filtered signal, wherein the analog-to-digital converter 105 The working bandwidth is greater than or equal to the bandwidth of the filtered signal.
  • the wireless communication device 1 further includes a carrier separator 106, which is used to separate the digital signal obtained after the analog-to-digital conversion operation to obtain the signal of the first carrier and the signal of the second carrier.
  • a carrier separator 106 which is used to separate the digital signal obtained after the analog-to-digital conversion operation to obtain the signal of the first carrier and the signal of the second carrier.
  • the wireless communication device 1 may further include: a device/module that processes the signal of the first carrier and the signal of the second carrier in the digital domain.
  • a device/module that processes the signal of the first carrier and the signal of the second carrier in the digital domain.
  • the wireless communication device 1 may be integrated in a radio frequency chip, or one part is integrated in a radio frequency chip, and the other part is integrated in a baseband chip.
  • the radio frequency front-end channel 101, the local oscillator circuit 102, the mixer circuit 103, the filter 104, or the analog-to-digital converter 105 (such as the local oscillator circuit 102 and the mixer circuit 103) is integrated in the radio frequency chip;
  • the splitter 106 is integrated in the baseband chip.
  • the wireless communication device 1 is a radio frequency chip.
  • the wireless communication device 1 is a terminal.
  • the wireless communication device 1 is a network device such as a base station.
  • the broadband radio frequency signal may also include a third carrier.
  • the third carrier may be continuous or discontinuous with the first carrier; or, continuous or discontinuous with the second carrier.
  • the third carrier may also be continuous with the first carrier or continuous with the second carrier. The embodiment of the present application does not limit this.
  • the first carrier and the second carrier are carriers of the same communication standard.
  • the first carrier and the second carrier may be in the same frequency band, as shown in FIG. 3.
  • one of the first carrier and the second carrier may be carrier CC1 in FIG. 3, and the other carrier may be carrier CC2 in FIG. 3.
  • the first carrier and the second carrier are two component carriers of the discontinuous carrier aggregation of the LTE system, which helps reduce the design complexity of the wireless communication device in the LTE system and save hardware resources in the LTE system.
  • the first carrier and the second carrier are two component carriers of the discontinuous carrier aggregation of the NR system, which helps to reduce the design complexity of the wireless communication device in the NR system and save hardware resources in the NR system.
  • the first carrier and the second carrier belong to the millimeter wave frequency band, which of course is not limited thereto.
  • the first carrier and the second carrier are carriers of different communication standards.
  • the first carrier is the carrier of the LTE system
  • the second carrier is the carrier of the NR system
  • the first carrier and the second carrier are two carriers that are dual-connected.
  • the frequency band where the first carrier is located is the same as the frequency band where the second carrier is located (specifically, it refers to the same number or the same spectrum resource).
  • the first carrier may be the LTE CC in FIG. 4A
  • the second carrier may be the NR CC in FIG. 4A.
  • the frequency band where the first carrier is located includes frequency band 3
  • the frequency band where the second carrier is located includes frequency band n3.
  • the frequency band where the first carrier is located includes frequency band 41
  • the frequency band where the second carrier is located includes frequency band n41.
  • the frequency band where the first carrier is located is different from the frequency band where the second carrier is located (specifically referring to different numbers and/or different spectrum resources), and there is no overlap between the two frequency bands.
  • the first carrier may be the LTE CC in FIG. 4B
  • the second carrier may be the NR CC in FIG. 4B.
  • the frequency band where the first carrier is located is different from the frequency band where the second carrier is located (specifically referring to different numbers and/or different spectrum resources), and there is overlap between the two frequency bands.
  • the frequency band of one of the first carrier and the second carrier completely covers the frequency band of the other carrier.
  • the frequency band where the first carrier is located includes frequency band 42
  • the frequency band where the second carrier is located includes frequency band n78.
  • the first carrier may be the LTE CC in FIG. 4C
  • the second carrier may be the NR CC in FIG. 4C.
  • the frequency band where the first carrier is located includes frequency band 42
  • the frequency band where the second carrier is located includes frequency band n77.
  • the signal bandwidths of the first carrier and the second carrier may be equal or unequal.
  • the wireless communication device 1 including a zero-IF architecture or a superheterodyne architecture as an example, the specific implementation of the wireless communication device 1 will be described.
  • FIG. 6 it is a schematic diagram of a structure when the wireless communication device 1 adopts a zero-IF architecture.
  • Figure 6 it is a schematic diagram of a structure when the wireless communication device 1 adopts a zero-IF architecture.
  • the radio frequency front-end channel 101 includes: a radio frequency filter 1011 and a first amplifier 1012.
  • the difference from the above-mentioned filter 104 is that the radio frequency filter 1011 is a filter that performs a filtering operation on the broadband radio frequency signal RX_IN, and sends the filtered signal to the first amplifier 1012.
  • the first amplifier 1012 is used to amplify the received signal and send the amplified signal to the mixer circuit 103.
  • the frequency of the local oscillator signal generated by the local oscillator circuit 102 is denoted as f LO .
  • the mixing circuit 103 is specifically configured to perform a down-conversion operation on the received signal sent by the first amplifier 1012 to obtain a baseband signal.
  • the imaginary part of the baseband signal is marked as IMIX_OUT, and the real part is marked as QMIX_OUT.
  • the imaginary part IMIX_OUT of the baseband signal is processed by one filter 104 to obtain the imaginary signal IABB_OUT, and the real part QMIX_OUT of the baseband signal is processed by another filter 104 to obtain the real signal QABB_OUT.
  • the imaginary signal IABB_OUT is processed by an analog-to-digital converter 105 to obtain the imaginary signal RX_IBB, and the real signal QABB_OUT is processed by another to obtain the real signal RX_QBB.
  • the imaginary part signal RX_IBB is processed by the carrier separator 106 to obtain the imaginary part CC1_IBB of the signal of the first carrier and the imaginary part CC2_IBB of the signal of the second carrier.
  • the real part signal RX_QBB is processed by the carrier separator 106 to obtain the real part CC1_QBB of the signal of the first carrier and the real part CC2_QBB of the signal of the second carrier.
  • CC1_IBB and CC1_QBB are jointly used to characterize the signal of the first carrier (specifically, the digital signal of the first carrier).
  • CC2_IBB and CC2_QBB are jointly used to characterize the signal of the second carrier (specifically, the digital signal of the second carrier).
  • FIG. 7 it is a schematic diagram of the frequency spectrum of the signal of each node in the working process of the wireless communication device 1 shown in FIG. 6.
  • the nodes here are defined for the convenience of description, specifically A, B, C, D1, and D2 in Figure 6.
  • the signal at node A represents the wideband radio frequency signal RX_IN received by the radio frequency front-end channel 101.
  • the signal RX_IN contains discontinuous frequency components of CC1 and CC2.
  • the frequency f LO of the local oscillator signal is located between the center frequencies f CC1 and f CC1 of CC1 and CC2.
  • the signal at node B represents the signal obtained after processing by the mixer circuit 103. Compared with the signal at node A, the frequency spectrum of the signal at node B uniformly reduces f LO .
  • the signal at node C represents the signal obtained by processing the signal output by the mixer circuit 103 by the filter 104 and the analog-to-digital converter 105.
  • the spectrum widths of the signals at node B and node C are the same, the value of the center frequency of CC1 is the same, and the value of the center frequency of CC2 is also the same.
  • the difference may include: the signal at node B is an analog signal, and the signal at node C is a digital signal.
  • the signal at the node D1 represents the signal of CC1 output by the carrier separator 106.
  • the signal at the node D2 indicates that it is the signal of CC2 output by the carrier separator 106.
  • the carrier separator 106 refer to the following. Based on the following description of the specific example of the carrier separator 106, it can be known that the value of the center frequency of the signal output by the carrier separator 106 is 0 (or close to 0).
  • the structure of the wireless communication device 1 shown in FIG. 6 is only an example, and it does not limit the structure of the wireless communication device 1 to which the embodiment of the present application is applicable.
  • the wireless communication device 1 may further include a method for processing a digital signal obtained through an analog-to-digital conversion operation, and sending the signal obtained after the processing to the carrier separator 106.
  • the broadband radio frequency signal received by the radio frequency front-end channel 101 also includes a third carrier
  • the imaginary signal RX_IBB is processed by the carrier separator 106 to obtain the signal of the first carrier.
  • the imaginary part of the signal of the second carrier and the imaginary part of the signal of the third carrier; the real part of the signal RX_QBB is processed by the carrier separator 106 to obtain the real part of the signal of the first carrier and the real part of the signal of the second carrier Part and the real part of the signal of the third carrier.
  • the working bandwidth of the devices/modules (such as the filter 104 and the analog-to-digital converter 105) in the wireless communication device 1 is sufficient (that is, greater than or equal to the broadband radio frequency signal).
  • a local oscillator signal is used, and the filter 104 is used to process the real and imaginary parts of the signal, and the real part is used to process the signal.
  • the analog-to-digital converter 105 of the part and imaginary part can realize the processing of broadband radio frequency signals containing frequency components of multiple discontinuous carriers. The greater the number of non-contiguous carriers, the more obvious the effect of reducing the design complexity of the wireless communication device and saving hardware resources of the technical solution provided by the embodiments of the present application.
  • FIG. 8 it is a schematic diagram of a structure when the wireless communication device 1 adopts a superheterodyne architecture.
  • Figure 8
  • the RF front-end channel 101 includes: a second amplifier 1013, a phase shifter 1014, a combiner 1015, a second mixer circuit 1016, a second local oscillator circuit 1017, and a third amplifier 1018.
  • the radio frequency front-end channel 101 is mainly used to complete the reception of a broadband radio frequency signal and the first down-conversion operation.
  • the mixing circuit 103 is mainly used to complete the second down-conversion operation.
  • the broadband radio frequency signal received by the radio frequency front-end channel 101 is amplified by the second amplifier 1013, and each amplified signal passes through a phase shifter 1014 for phase adjustment.
  • the signals multiplexed through the phase shifter 1014 are combined by the combiner 1015 and then sent to the second mixing circuit 1016.
  • the second mixing circuit 1016 is used for down-converting the received signal.
  • the local oscillator signal used is generated by the second local oscillator circuit 1017.
  • the third amplifier 1018 is used to amplify the signal (ie, the intermediate frequency signal) output by the second mixer circuit 1016 and send the amplified signal to the mixer circuit 103.
  • FIG. 9 it is a schematic diagram of the signals of each node in the working process of the wireless communication device 1 shown in FIG. 8.
  • the nodes here are defined for the convenience of description, and these nodes specifically refer to A, B, C, D, E1, and E2 in FIG. 8. The following describes the signals of each node in Figure 9:
  • the signal at node A represents the wideband radio frequency signal RX_IN received by the radio frequency front-end channel 101.
  • the signal RX_IN contains discontinuous frequency components of CC1 and CC2.
  • f HF represents the center frequency of RX_IN.
  • the signal at node B represents the signal obtained after processing by the second mixer circuit 1016.
  • the frequency spectrum of the signal at node B uniformly reduces f HF_LO .
  • f HF_LO is greater than 0.
  • the center frequency of the carrier aggregation signal is reduced from f HF to f IF .
  • f IF f HF -f HF_LO .
  • the embodiment of the present application does not limit how to obtain the value of f HF_LO , and for details, reference may be made to the prior art.
  • the signal at node C represents the signal obtained after processing by the mixer circuit 103.
  • the frequency spectrum of the signal at node C is uniformly reduced by f IF , so that the center frequency of the carrier aggregation signal is reduced from f IF to 0.
  • the center frequencies of the signals of CC1 and CC2 are reduced to f CC1 -f LO and f CC2 -f LO respectively .
  • f HF_LO + f IF f LO .
  • the signal at node D in FIG. 8 can refer to the signal at node C shown in FIG. 7 above.
  • the signals of the node E1 and the node E2 in FIG. 8 can refer to the signals of the node D1 and the node D2 shown in FIG. 7 above.
  • the functions performed by the local oscillator circuit 102, the mixer circuit 103, the filter 104, the analog-to-digital converter 105, and the carrier separator 106 in FIG. 8 can all refer to the embodiment shown in FIG. 6, and will not be repeated here.
  • the second mixing circuit 1016 may be referred to as a high-frequency mixing circuit, and the above-mentioned mixing circuit 103 may be referred to as an intermediate frequency mixing circuit.
  • the second local oscillation circuit 1017 may be called a high-frequency local oscillation circuit, and the above-mentioned local oscillation circuit 102 may be called an intermediate frequency local oscillation circuit.
  • Solution 1 The frequency value of the local oscillator signal generated by the mixing circuit 103 is determined based on the highest center frequency and the lowest center frequency of the carrier contained in the broadband radio frequency signal.
  • the frequency of the local oscillator signal generated by the mixing circuit 103 is set to be the middle frequency between the highest center frequency and the lowest center frequency of the carrier included in the broadband radio frequency signal.
  • the broadband radio frequency signal contains the above-mentioned first carrier (marked as CC1) and second carrier (marked as CC2), a total of 2 discontinuous carriers, and the frequency points of the first carrier and the second carrier are respectively marked as f CC1 and f CC2 ,
  • the frequency value f LO of the local oscillator signal generated by the mixing circuit 103 satisfies the following formula:
  • the broadband radio frequency signal contains the frequency components of the following carriers: CC1, CC2,...CCn
  • the center frequencies of these carriers are f CC1 , f CC2 ,...f CCn
  • n is an integer greater than or equal to 2.
  • the size of the center frequency satisfies f CC1 ⁇ f CC2 ⁇ ... ⁇ f CCn ; then, the frequency value f LO of the local oscillator signal generated by the mixer circuit 103 satisfies the following formula:
  • Solution 2 The frequency value of the local oscillator signal generated by the mixing circuit 103 is determined based on the intermediate frequency of the broadband radio frequency signal.
  • the frequency of the local oscillator signal generated by the mixing circuit 103 is the middle frequency of the broadband radio frequency signal.
  • the broadband radio frequency signal contains the above-mentioned first carrier (marked as CC1) and second carrier (marked as CC2), a total of 2 discontinuous carriers, and the frequency points of the first carrier and the second carrier are respectively marked as f CC1 and f CC2 ,
  • the signal bandwidth is marked as BW CC1 and BW CC2 as an example, the bandwidth BW CA of the broadband radio frequency signal satisfies the formula: It can be seen that the frequency value f LO of the local oscillator signal generated by the mixer circuit 103 satisfies the following formula:
  • the broadband radio frequency signal contains the frequency components of the following carriers: CC1, CC2,...CCn
  • the center frequencies of these carriers are f CC1 , f CC2 ,...f CCn
  • their signal bandwidths are BW CC1 , BW CC2, respectively ,...BW CCn , where n is an integer greater than or equal to 2.
  • the size of these center frequencies satisfies f CC1 ⁇ f CC2 ⁇ ... ⁇ f CCn ; then, the frequency value f LO of the local oscillator signal generated by the mixer circuit 103 satisfies the following formula:
  • the working bandwidths of the filter 104 and the analog-to-digital converter 103 may be equal or unequal. In the specific implementation, the two are generally designed to be equal, and the following description is based on the equality of the two as an example.
  • the design principle of the working bandwidth of the filter 104 and the analog-to-digital converter 103 is to satisfy the lossless signal transmission. Since the filter 104 and the analog-to-digital converter 103 process real-number signals, their bandwidth characteristics are all symmetrical about the zero frequency, so:
  • BW LFP1 can satisfy the following formula:
  • the signal bandwidth of CC1 is greater than the signal bandwidth of CC2.
  • the graph a in FIG. 10 represents the signal at the node A in FIG. 6.
  • the b diagram in FIG. 10 represents the signal at the node B in FIG. 6.
  • the working bandwidth of the filter 104 and the analog-to-digital converter 103 is BW LFP1 .
  • the working bandwidth BW LFP2 of the filter 104 and the analog-to-digital converter 103 can satisfy the following formula:
  • the signal bandwidth of CC1 is greater than the signal bandwidth of CC2.
  • the graph a in FIG. 11 represents the signal at the node A in FIG. 6.
  • Diagram b in FIG. 11 represents the signal at node B in FIG. 6.
  • the working bandwidth of the filter 104 and the analog-to-digital converter 103 is BW LFP2 .
  • the frequency value of the local oscillator signal should be determined by a reasonable choice.
  • the second scheme above is selected to determine the frequency value of the local oscillator signal, which helps to reduce the filter 104 And the working bandwidth of the analog-to-digital converter 103, thereby helping to reduce the power consumption of the wireless communication device.
  • the embodiment of the present application does not limit the specific implementation manner of the carrier separator 106. As shown in FIG. 11, it is a schematic structural diagram of a carrier separator 106 applicable to the embodiments of the present application.
  • the carrier separator 106 includes: a first digital frequency converter 201, a second digital frequency converter 202, a first sample rate converter (SRC) 203, and a second SRC 204.
  • SRC sample rate converter
  • the function of each device/module in the carrier separator 106 is described below based on FIG. 6.
  • the first digital frequency converter 201 is used to change the frequency of the signal at node C in FIG. 6 so that the signal of the first carrier in the signal is moved to the baseband, and then the frequency-changed signal is sent to the first digital
  • the inverter 201 is connected to the first SRC202.
  • the first SRC202 is used to reduce the sampling rate of the received signal to the sampling rate required by the first carrier (the sampling rate may be predefined), and in the process of reducing the sampling rate, filter out other carriers (such as the second carrier, etc.), and the redundant frequency components between the carriers, to obtain the signal of the first carrier (specifically, a digital signal).
  • the second digital frequency converter 203 is used to change the frequency of node C in FIG. 6 so that the signal of the second carrier in the signal is moved to the baseband, and then the frequency-changed signal is sent to the second digital frequency converter 203 Connected to the second SRC204.
  • the second SRC204 is used to reduce the sampling rate of the received signal to the sampling rate required by the second carrier (the sampling rate may be predefined), and in the process of reducing the sampling rate, it will filter out the first The carrier, and the redundant frequency components between the first carrier and the second carrier, obtain the signal of the second carrier (specifically, a digital signal).
  • a digital frequency converter can complete the movement of a digital signal corresponding to a carrier. After the digital inverter, the desired carrier is moved to the baseband, but other carriers and useless frequency components are still retained. Since the digital converter still operates on all discontinuous aggregated carriers output by the analog-to-digital converter 105, the sampling rate of the signal is not changed. Therefore, after the digital inverter, SRC202 needs to be introduced for down-sampling rate processing, and during the down-sampling operation, other components other than the expected carrier are filtered out.
  • FIG. 13 it is a schematic diagram of the signals of each node in the carrier separator 106 shown in FIG. 12.
  • the nodes in Figure 12 are drawn based on Figure 7.
  • the signals at the node C, the node D1, and the node D2 in FIG. 12 correspond to the signals at the node C, the node D1, and the node D2 in FIG. 7 respectively.
  • nodes E1 and E2 are marked in FIG. 12, and the signals at the nodes E1 and E2 are shown in FIG. 13.
  • the signal at the node E1 is the signal of the node C.
  • the frequency spectrum of the signal at the node C is uniformly reduced by f CC1 -f LO , so that the center frequency of the carrier CC1 is reduced to zero.
  • the center frequency of the carrier CC2 is f CC2- f CC1 .
  • the signal at the node D1 is the signal of the first carrier obtained after filtering the second carrier in the signal at the node E1 and the redundant carrier between the first carrier and the second carrier.
  • the signal at the node E2 is the signal of the node C.
  • the frequency spectrum of the signal at the node C is uniformly reduced by f CC2 -f LO , so that the center frequency of the carrier CC2 is reduced to zero.
  • the center frequency of the carrier CC1 is f CC1- f CC2 .
  • the signal at the node D2 is a signal of the second carrier obtained after filtering the first carrier in the signal at the node E2 and the redundant carrier between the first carrier and the second carrier.
  • the first digital frequency converter 201 includes:
  • the first numerically controlled oscillator (NCO) 2011 is used to generate the local oscillator signal NCO1, where NCO1 is composed of a set of mutually orthogonal monophonic signals NCOI/NCOQ (for example, NCOI is a cosine signal, and NCOQ is Sinusoidal signal. The two signals are 90 degrees out of phase).
  • the complex multiplier 2012 is used to perform a complex multiplication operation with the digital signal output by the analog-to-digital converter 105 through the digital local oscillator signal NCO1.
  • the first carrier can be moved to the baseband respectively.
  • the second digital frequency converter 203 includes:
  • the second numerically controlled oscillator 2031 is used to generate a local oscillator signal NCO2, where NCO2 is a set of mutually orthogonal monophonic signals.
  • the frequency of this group of NCOI/NCOQ is the center frequency of the second carrier output from the analog-to-digital converter 105.
  • the complex multiplier 2032 is used to perform a complex multiplication operation with the digital signal output by the analog-to-digital converter 105 through the digital local oscillator signal NCO2.
  • the second carrier can be moved to the baseband respectively.
  • the Nyquist frequency of the signal is half of the signal sampling rate.
  • the data sampling rate f s of the analog-to-digital converter 105 needs to satisfy: f s > 2 ⁇ BW LPF .
  • the Nyquist frequency f NC of the signal output by the analog-to-digital converter 105 needs to satisfy: f NC >BW LPF . Since the output of the carrier separator 106 is the signal on each independent carrier, the bandwidth is BW CC1 and BW CC2 respectively . Therefore, taking the non-contiguously aggregated carrier including the first carrier and the second carrier as an example, the output of the carrier separator 106 It is the Nyquist frequency of the signal of the first carrier and the second carrier that needs to meet:
  • the carrier separator 106 Since the larger the spectral bandwidth of the signal, the higher the Nyquist frequency required, and the greater the cost of the power consumption required by the processing circuit. Based on the above analysis, it can be known that after the carrier separation operation is performed by the carrier separator 106, the required Nyquist frequency is also reduced, which helps to reduce the cost of signal processing.
  • the carrier output of the carrier separator 106 since the processed signal is an independent carrier, and the bandwidth of each carrier is smaller than the total bandwidth of the signal output by the analog-to-digital converter 105, the carrier output of the carrier separator 106 The sampling rate on the node is less than the sampling rate of the node signal output by the analog-to-digital converter 105.
  • the carrier separator 106 separates the non-contiguously aggregated multiple carriers input to the wireless communication device 1 into multiple independent carriers.
  • FIGS. 11 to 13 two carrier units are taken as examples to illustrate the working principle of the carrier separator 106. For the scenario of discontinuous aggregation of more carriers, this can be extended accordingly.
  • a schematic flowchart of a signal processing method provided by an embodiment of this application, which is applied to a wireless communication device, and the method may include:
  • the wireless communication device receives a broadband radio frequency signal, and the broadband radio frequency signal contains non-continuous signal frequency components of the first carrier and the second carrier.
  • the wireless communication device generates a local oscillator signal.
  • the wireless communication device performs a down-conversion operation on the broadband radio frequency signal according to the local oscillator signal to obtain a baseband signal.
  • the wireless communication device performs a filtering operation on the baseband signal to obtain a filtered signal.
  • the bandwidth of the filtered signal includes the signal bandwidth of the first carrier, the signal bandwidth of the second carrier, and the redundancy bandwidth between the first carrier and the second carrier.
  • the wireless communication device performs an analog-to-digital conversion operation on the filtered signal, where the working bandwidth of the analog-to-digital converter used when performing the analog-to-digital conversion operation is greater than or equal to the bandwidth of the filtered signal.
  • the wireless communication device separates the digital signal obtained after the analog-to-digital conversion operation to obtain a signal of the first carrier and a signal of the second carrier.
  • the specific implementation of the wireless communication device the specific implementation of the first carrier and the second carrier, the specific implementation of the frequency of the local oscillator signal, etc., as well as the beneficial effects that the method can bring, please refer to the above, here No longer.
  • the above embodiments it may be implemented in whole or in part by software, hardware, firmware, or any combination thereof.
  • a software program it can be implemented in the form of a computer program product in whole or in part.
  • the computer program product includes one or more computer instructions.
  • the computer execution instructions When the computer execution instructions are loaded and executed on the computer, the processes or functions according to the embodiments of the present application are generated in whole or in part.
  • the computer may be a general-purpose computer, a special-purpose computer, a computer network, or other programmable devices.
  • Computer instructions may be stored in a computer-readable storage medium, or transmitted from one computer-readable storage medium to another computer-readable storage medium.
  • computer instructions may be transmitted from a website, computer, server, or data center through a cable (such as Coaxial cable, optical fiber, digital subscriber line (digital subscriber line, DSL) or wireless (such as infrared, wireless, microwave, etc.) transmission to another website site, computer, server or data center.
  • the computer-readable storage medium may be any available medium that can be accessed by a computer, or may include one or more data storage devices such as a server or a data center that can be integrated with the medium.
  • the usable medium may be a magnetic medium (for example, a floppy disk, a hard disk, and a magnetic tape), an optical medium (for example, a DVD), or a semiconductor medium (for example, a solid state disk (SSD)).

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Abstract

本申请公开了无线通信装置及信号处理方法，涉及通信技术领域，用于对多个不连续的载波上承载的信号进行处理，有助于降低无线通信装置的设计复杂度，以及节省硬件资源。无线通信装置，包括：射频前端通道，用于接收宽带射频信号，宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分。本振电路，用于产生本振信号。与射频前端通道和本振电路耦合的混频电路，用于根据本振信号对宽带射频信号进行下变频操作，以得到基带信号。与混频电路耦合的滤波器，用于对基带信号进行滤波操作，以得到经滤波的信号。经滤波的信号的带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。

Description

无线通信装置及信号处理方法 技术领域
本申请涉及通信技术领域，尤其涉及无线通信装置及信号处理方法。
背景技术
随着无线通信技术的发展，为了满足终端峰值速率和系统容量的要求，在长期演进增强(long term evolution-advance，LTE-A)系统和新无线电(new radio，NR)系统中，引入了载波聚合(carrier aggregation，CA)技术，以通过扩展无线传输带宽，为终端分配更多的无线频谱资源，从而提升吞吐率。基于CA技术，网络设备可以根据终端对业务量的需求，动态给终端分配一个或多个载波。
由于部分运营商拥有的频谱资源不是连续的，为了给终端提供足够的频谱资源以支持期望的通信业务，需要将分离的频谱聚合在一起使用。因此，在频谱不连续的场景(即网络设备给终端分配的多个载波不连续的场景)中，如何设计无线通信装置，以对多个不连续的载波上承载的信号进行处理，成为亟待解决的技术问题。
发明内容
本申请实施例提供了无线通信装置及信号处理方法，用于对多个不连续的载波上承载的信号进行处理，有助于降低无线通信装置的设计复杂度，以及节省硬件资源。
第一方面，提供了一种无线通信装置，包括：射频前端通道，用于接收宽带射频信号，宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分。本振电路，用于产生本振信号。与射频前端通道和本振电路耦合的混频电路，用于根据本振信号对宽带射频信号进行下变频操作，以得到基带信号。与混频电路耦合的滤波器，用于对基带信号进行滤波操作，以得到经滤波的信号。经滤波的信号的带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。
第二方面，还提供了一种无线通信装置，包括：
混频电路，用于接收宽带射频信号和本振信号，并根据该本振信号对该宽带射频信号进行下变频操作，以得到基带信号，其中，该宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分；
滤波器，用于对该基带信号进行滤波操作，以得到经滤波的信号，该经滤波的信号的带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。
与第一方面相比，第二方面中，射频前端通道是可选的，本振电路也是可选的。
本技术方案中，对“带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽”的宽带射频信号进行下变频操作和滤波操作之后，所得到的信号的带宽中仍包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。这样，一方面，在执行下变频操作时，基于一个本振信号，即可得到待执行滤波操作的基带信号。另一方面，在执行滤波操作时，对所生成的一路基带信号进行滤波即可。因此，有助于减少本振信号的数量以 及滤波操作的执行次数，从而有助于降低无线通信装置的设计复杂度。另外，在硬件实现上，有助于减少生成本振信号所使用的本振电路的个数和执行滤波操作所使用的滤波器的个数，从而有助于节省硬件资源。
上述宽带射频信号是相对单个载波的射频信号进行说明的，在此统一说明。
在一种可能的设计中，第一载波和第二载波为长期演进系统的非连续载波聚合的两个成员载波。这有助于降低长期演进系统中无线通信装置的设计复杂度，并且节省长期演进系统中的硬件资源。
在一种可能的设计中，第一载波和第二载波为新无线电系统的非连续载波聚合的两个成员载波。这有助于降低新无线电系统中无线通信装置的设计复杂度，并且节省新无线电系统中的硬件资源。
在一种可能的设计中，第一载波和第二载波属于毫米波频段。也就是说，本申请实施例提供的技术方案可以适用于毫米波频段。当然不限于此。
在一种可能的设计中，第一载波和第二载波在同一频带内。这有助于降低对滤波器的工作带宽的要求，从而有助于节省滤波器的功率开销，进而节省无线通信装置的整体功率开销。
在一种可能的设计中，第一载波为长期演进系统的载波，第二载波为新无线电系统的载波，第一载波和第二载波是双连接的两个载波。也就是说，本申请实施例提供的技术方案可以适用于双连接工作模式中。
在一种可能的设计中，第一载波所在的频带与第二载波所在的频带相同。这有助于降低对滤波器的工作带宽的要求，从而有助于节省滤波器的功率开销，进而节省无线通信装置的整体功率开销。例如，第一载波所在的频带包括频带3，第二载波所在的频带包括频带n3。又如，第一载波所在的频带包括频带41，第二载波所在的频带包括频带n41。
在一种可能的设计中，第一载波所在的频带与第二载波所在的频带不相同，但有重叠。这有助于降低对滤波器的工作带宽的要求，从而有助于节省滤波器的功率开销，进而节省无线通信装置的整体功率开销。
在一种可能的设计中，第一载波所在的频带与第二载波所在的频带不相同，但第一载波所在的频带完全覆盖第二载波所在的频带，或者第二载波所在的频带完全覆盖第一载波所在的频带。例如，第一载波所在的频带包括频带42，第二载波所在的频带包括频带n77。又如，第一载波所在的频带包括频带42，第二载波所在的频带包括频带n78。
在一种可能的设计中，本振信号的频率取值为宽带射频信号中包含的载波的最高中心频率与最低中心频率的中间频率。
在一种可能的设计中，本振信号的频率取值为宽带射频信号的中间频率。
在一种可能的设计中，无线通信装置还包括：与滤波器耦合的模数转换器，用于对经滤波的信号进行模数转换操作，其中，模数转换器的工作带宽大于或等于经滤波的信号的带宽。相比对单个载波进行处理(如对第一载波或第二载波单独进行处理)的技术方案，本申请实施例中的模数转换器的工作带宽更宽。
在一种可能的设计中，无线通信装置还包括：载波分离器，用于将模数转换操作 后得到的数字信号进行分离，得到第一载波的信号和第二载波的信号。相比载波聚合的数字信号来说，单个载波的数字信号的带宽相对较小，因此需要的奈奎斯特频率也降低了，这有助于降低后续信号处理的代价。
在一种可能的设计中，本振电路和混频电路集成在射频芯片中，载波分离器集成在基带芯片中。
在一种可能的设计中，无线通信装置集成在射频芯片中。
在一种可能的设计中，无线通信装置为终端或基站。
上述均是以宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分为例进行说明的，实际实现时，宽带射频信号中还可以包括非连续的三个或三个以上的载波的信号频率成分。基于此，无线通信装置的设计原理可以基于上文中所描述的技术方案推理得到，此处不再赘述。
第二方面，提供了一种信号处理方法，应用于无线通信装置，该方法包括：接收宽带射频信号，宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分；产生本振信号；根据本振信号对宽带射频信号进行下变频操作，以得到基带信号；对基带信号进行滤波操作，以得到经滤波的信号；经滤波的信号的带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。
关于第一载波、第二载波、本振信号的频率取值，以及无线通信装置的具体实现方式可以参考上述第一方面，此处不再赘述。
在一种可能的设计中，该方法还包括：对经滤波的信号进行模数转换操作，其中，执行模数转换操作时所使用的模数转换器的工作带宽大于或等于经滤波的信号的带宽。
在一种可能的设计中，该方法还包括：将模数转换操作后得到的数字信号进行分离，得到第一载波的信号和第二载波的信号。
第三方面，提供了一种信号处理装置，用于执行上述第二方面或第二方面提供的任一种信号处理方法。该信号处理装置可以是上述无线通信装置，或芯片，或终端或网络设备(如基站)。
在一种可能的设计中，该装置包括用于执行第二方面或第二方面任一种可能的设计提供的方法的各个模块。
在一种可能的设计中，该装置包括存储器和处理器，存储器用于用于存储计算机程序，处理器用于调用该计算机程序，以执行第二方面或第二方面任一种可能的设计所提供的方法。
第四方面，提供了一种计算机可读存储介质，其上储存有计算机程序，当该计算机程序被计算机调用时，使得计算机执行第二方面或其任一种可能的设计提供的方法。
第五方面，提供了一种计算机程序产品，当其在计算机上运行时，使得第二方面或其任一种可能的设计提供的方法被执行。
可以理解的是，上述提供的任一种信号处理方法、信号处理装置、计算机可读存储介质或计算机程序产品均用于执行上文所提供的对应的无线通信装置，因此，其所能达到的有益效果可参考对应的无线通信装置中的有益效果，此处不再赘述。
附图说明
图1A为可适用于本申请实施例的一种通信系统的示意图；
图1B为可适用于本申请实施例的另一种通信系统的示意图；
图2为可适用于本申请实施例的一种通信设备的硬件结构示意图；
图3为可适用于本申请实施例的一种NC-CA工作模式下的频谱示意图；
图4A为可适用于本申请实施例的一种频带内非连续EN-DC工作模式下的频谱示意图；
图4B为可适用于本申请实施例的一种频带间非连续EN-DC工作模式下的频谱示意图；
图4C为可适用于本申请实施例的另一种频带间非连续EN-DC工作模式下的频谱示意图；
图5为本申请实施例提供的一种无线通信装置的结构示意图；
图6为本申请实施例提供的另一种无线通信装置的结构示意图；
图7为本申请实施例提供的一种图6所示的无线通信装置的工作过程中各节点的信号的频谱示意图；
图8为本申请实施例提供的另一种无线通信装置的结构示意图；
图9为本申请实施例提供的一种图8所示的无线通信装置的工作过程中各节点的信号的频谱示意图；
图10为本申请实施例提供的一种滤波器和模数转换器的工作带宽的示意图；
图11为本申请实施例提供的另一种滤波器和模数转换器的工作带宽的示意图；
图12为本申请实施例提供的一种载波分离器的结构示意图；
图13为本申请实施例提供的一种图12中的载波分离器的工作过程中各节点的信号的频谱示意图；
图14为本申请实施例提供的另一种载波分离器的结构示意图；
图15为本申请实施例提供的一种信号处理方法的流程示意图。
具体实施方式
本申请实施例提供的技术方案可以应用于各种通信系统，例如，第五代(5th generation，5G)移动通信系统如5G NR系统中，未来演进系统或多种通信融合系统等中，也可以应用于在现有通信系统如LTE通信系统中。本申请提供的技术方案的应用场景可以包括多种，例如，机器对机器(machine to machine，M2M)、宏微通信、增强型移动互联网(enhanced mobile broadband，eMBB)、超高可靠性与超低时延通信(ultra reliable&low latency communication，uRLLC)以及海量物联网通信(massive machine type communication，mMTC)等场景。这些场景可以包括但不限于包括：终端与终端之间的通信场景，网络设备与网络设备之间的通信场景，网络设备与终端之间的通信场景等。
图1A为可适用于本申请一实施例的通信系统的示意图，该通信系统包括一个或多个网络设备10(仅示出了1个)以及与每一网络设备10连接的一个或多个终端20。
图1B为可适用于本申请另一实施例的通信系统的示意图，该通信系统包括一个或多个网络设备10以及一个或多个终端20。其中，一个终端20可以与多个网络设备10连接。该多个网络设备10中的不同网络设备可以支持不同的通信制式，例如，如图1B中所示，其中一个网络设备10是LTE基站，另一个网络设备10是NR基站。
图1A和图1B仅为示意图，并不构成对本申请提供的技术方案的适用场景的限定。
网络设备10可以是传输接收节点(transmission reception point，TRP)、基站、中继站或接入点等。网络设备10可以是5G通信系统中的网络设备或未来演进网络中的网络设备；还可以是可穿戴设备或车载设备等。另外还可以是：全球移动通信系统(global system for mobile communication，GSM)或码分多址(code division multiple access，CDMA)网络中的基站收发信台(base transceiver station，BTS)，也可以是宽带码分多址(wideband code division multiple access，WCDMA)中的NB(NodeB)，还可以是长期演进(long term evolution，LTE)中的eNB或eNodeB(evolutional NodeB)。网络设备10还可以是云无线接入网络(cloud radio access network，CRAN)场景下的无线控制器。
终端20可以是用户设备(user equipment，UE)、接入终端、UE单元、UE站、移动站、移动台、远方站、远程终端、移动设备、UE终端、无线通信设备、UE代理或UE装置等。接入终端可以是蜂窝电话、无绳电话、会话发起协议(session initiation protocol，SIP)电话、无线本地环路(wireless local loop，WLL)站、个人数字处理(personal digital assistant，PDA)、具有无线通信功能的手持设备、计算设备或连接到无线调制解调器的其它处理设备、车载设备、可穿戴设备，5G网络中的终端或未来演进的公共陆地移动网络(public land mobile network，PLMN)网络中的终端等。
可选的，图1A和图1B中的各网元(例如网络设备10和终端20等)均可以通过图2中的通信设备200来实现。图2为可适用于本申请一实施例的通信设备的硬件结构示意图。该通信设备200可以包括201部分以及和202部分。201部分主要用于射频信号的收发以及射频信号与基带信号的转换等。202部分主要用于基带信号的处理，以及对通信设备20的控制等。201部分通常可以称为收发单元、收发机、收发电路、或者收发器等。202部分通常是通信设备200的控制中心，通常可以称为处理单元。
201部分可以包括天线2011和射频单元2012。其中，射频单元2012主要用于进行射频处理。可选的，可以将201部分中用于实现接收功能的器件视为接收单元，将用于实现发送功能的器件视为发送单元，即201部分包括接收单元和发送单元。接收单元也可以称为接收机、接收器、或接收电路等，发送单元可以称为发射机、发射器或者发射电路等。
202部分可以包括一个或多个单板，每个单板可以包括一个或多个处理器2021和一个或多个存储器2022。处理器2021用于读取和执行存储器2022中的程序以实现基带处理功能以及对通信设备200的控制。若存在多个单板，各个单板之间可以互联以增加处理能力。作为一种可选的实施方式，也可以是多个单板共用一个或多个处理器2021，或者是多个单板共用一个或多个存储器2022，或者是多个单板同时共用一个或多个处理器2021。
射频单元2012可以包括射频芯片。202部分可以包括基带芯片。
上述的通信设备200可以是一个通用设备或者是一个专用设备。本申请实施例不限定通信设备200的类型。
以下，说明本申请实施例中所涉及的部分术语及技术，以方便读者理解。
1)、载波
载波是特定频率的无线电波。载波可以被称作载波单元(carrier component，CC)。
2)、基带信号，宽带射频信号
基带信号的信号频谱位于零点附近或接近零点，也可以称作“低频信号”。
宽带射频信号，是相对包含一个载波的信号频率成分的射频信号而言的。作为示例，在零中频架构中，宽带射频信号可以是中频信号。在超外差架构中，宽带射频信号可以是高频信号。
3)、非连续载波聚合(intra-band non-contiguous carrier aggregation，NC-CA)
为了支持在非连续频谱上进行无线通信，LTE协议和NR协议中均定义了NC-CA工作模式。在NC-CA工作模式中，定义了非连续载波聚合信号。
如图3所示，假设频带A(frequency band A)中包含两个载波(分别标记为CC1、CC2)，这两个载波的带宽分别为BW CC1和BW CC2，中心频率分别为f CC1和f CC2，且f CC2>f CC1，则当满足
Figure PCTCN2019128483-appb-000001
时，载波CC1、CC2，以及介于这两个载波之间的冗余频率成分定义为非连续载波聚合信号，图3中示意出了非连续载波聚合信号所占的频域资源。
图3是以2个载波的非连续载波聚合为例进行说明的。实际应用中，可能存在两个以上载波的非连续载波聚合，该情况下，该两个以上载波，以及该两个以上载波之间的冗余频率成分定义为非连续载波聚合信号。
4)、4G-5G双连接(E-UTRA/NR dual connectivity，EN-DC)
在NR系统中，为了进一步提升网络部署的灵活性，以及提升对运营商现有LTE网络的使用效率，专门定义了EN-DC工作模式，即终端可以同时连接NR基站和LTE基站，同时进行两种制式的通信，如图1B所示。
在EN-DC工作模式下，终端需要保持与LTE基站和NR基站的通信，即需要接收LTE基站下发的LTE制式的射频信号，以及通过NR基站下发的NR制式射频信号。这两种通信制式的射频信号，被分别分配在各自系统的工作频段内。
EN-DC信号的概念与上述非连续载波聚合信号的概念类似。二者的区别在于，非连续载波聚合信号中所涉及的载波均是同一种通信制式下的载波，如均是LTE载波或均是NR载波，而EN-DC中所涉及的部分载波是LTE载波，部分载波是NR载波。其中，LTE载波是LTE基站调用的载波，NR载波是NR基站调用的载波。
以下，说明EN-DC工作模式下，LTE信号(即LTE基站发送的信号)和NR信号(即NR基站发送的信号)所占的频段的应用场景：
应用场景1：LTE信号和NR信号被分配在相对应的频带内，即网络设备可以按照频带内EN-DC工作模式调度终端。
以下说明“相对应的频带”：由于NR系统与LTE系统之间有一定的继承性，因此，在频段分配及命名规则上有相关性。在通信标准中，NR系统与LTE系统编号相同的频带，频率覆盖范围是相同的。例如，LTE系统中，E-UTRA频带1的上行工作频率范围为1920MHz(兆赫兹)～1980MHz，下行工作频率范围为2110MHz～2170MHz；在NR系统中，NR频带n1的上行工作频率范围是1920MHz～1980MHz，下行工作频率范围是2110MHz～2170MHz。依此类推，NR系统与LTE系统中编号相同的其他频带也有类似的关系。在本申请实施例中，将NR系统与LTE系统中编号相同的频带称作是“相对应的频带”。
在频带内EN-DC工作模式中，当LTE信号和NR信号的频谱不是连续分配的时，该工作模式被定义为频带内非连续EN-DC(intra-band non-contiguous EN-DC)工作模式。频带内非连续EN-DC工作模式下频谱示意图如图4A所示。在图4A中，网络设备调用了一个LTE载波(标记为LTE CC)和一个NR载波(标记为NR CC)。LTE CC被分配在E-UTRA频带X内，其带宽为BW LTE_CC，中心频率为f LTE_CC。NR CC被分配在NR频带nX内，其带宽为BW NR_CC，中心频率为f NR_CC。E-UTRA频带X和NR频带nX的频率范围相同。
应用场景2：LTE信号和NR信号被分配在不相对应的频带内。这一类EN-DC工作模式，被定义为频带间EN-DC(inter-band EN-DC)工作模式。
在一种实现方式中，LTE载波被分配在E-UTRA频带X内，NR载波被分配在NR频带nY内，X与Y不相等，且频带X与频带nY之间没有重叠，如图4B所示。在图4B中，LTE CC被分配在E-UTRA频带X内，其带宽为BW LTE_CC，中心频率为f LTE_CC。NR CC被分配在NR频带nY内，其带宽为BW NR_CC，中心频率为f NR_CC。E-UTRA频带X和NR频带nX的频率范围之间没有重叠。
在另一种实现方式中，LTE载波被分配在E-UTRA频带X内，NR载波被分配在NR频带nY内，X与Y不相等，但是频带X与频带nY之间有重叠。在该实现方式中，名义上，LTE载波和NR载波被分配到了不同编码的频带上，但是它们的频谱之间有重叠，或者说频谱之间相互靠近(或接近)。
例如，这两个频带中的其中一个频带可以部分覆盖另一个频带。
又如，这两个频带中的其中一个频带可以完全覆盖另一个频带，如LTE系统中E-UTRA频带42的上、下行频率范围为3400MHz～3600MHz，NR系统中NR频带n78的上、下行频率覆盖范围为3300MHz～3800MHz，在频谱上，NR频带n78可以完全覆盖E-UTRA频带42，如图4C所示。在图4C中，LTE CC被分配在E-UTRA频带42内，其带宽为BW LTE_CC，中心频率为f LTE_CC。NR CC被分配在NR频带n78内，其带宽为BW NR_CC，中心频率为f NR_CC。
5)、零中频架构、超外差架构
零中频架构通常通过一次变频处理，将信号从射频载频搬移到基带。
超外差结构通常通过两次变频处理，将信号从射频载频搬移到基带。
需要说明的是，为了获得更宽带的频谱资源，支持更大吞吐率的通信业务，NR系统中引入了毫米波频段，即NR通信标准中定义的NR FR2(frequency range 2)频段，NR FR2为24.25GHz～52.60GHz。对于NR FR2频段，同样也存在频带内非连续载波聚合(NCCA)的应用场景，即在NR FR2的某一个频带内，同时存在2个或2个以上频谱不连续的载波单元。工作在NR FR2频段上的无线通信装置，通常会采用超外差架构。当然，具体实现时，超外差架构的无线通信装置的应用场景不限于此。
6)、其他术语
本申请实施例中的术语“至少一个(种)”包括一个(种)或多个(种)。
“多个(种)”是指两个(种)或两个(种)以上。例如，A、B和C中的至少一种，包括：单独存在A、单独存在B、同时存在A和B、同时存在A和C、同时存在B和C，以及同时存在A、B和C。
在本申请中，除非另有说明，“/”表示或的意思，例如，A/B可以表示A或B；本文中的“和/或”仅仅是一种描述关联对象的关联关系，表示可以存在三种关系，例如A和/或B，可以表示：单独存在A，同时存在A和B，单独存在B这三种情况。
为了便于清楚描述本申请实施例的技术方案，本申请的实施例中采用了“第一”、“第二”等字样对功能和作用基本相同的相同项或相似项进行区分。本领域技术人员可以理解“第一”、“第二”等字样并不对数量和执行次序进行限定，且“第一”、“第二”等字样也并不限定一定不同。
以下，结合附图，说明本申请实施例提供的技术方案。
如图5所示，为本申请实施例提供的一种无线通信装置1的结构示意图。无线通信装置1可以包括：
射频前端通道101，用于接收宽带射频信号，宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分。宽带射频信号的带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。射频前端通道101除了用于接收宽带射频信号之外，还可以用于对宽带射频信号进行处理，该处理具体是指该信号在进入混频电路103(用于得到基带信号的混频电路)之前的处理。例如，对宽带射频信号进行滤波操作、放大操作、高频混频操作或移相操作中的一种或多种。也就是说，射频前端通道101所包含的器件/模块是执行这些处理操作的模块。无线通信装置1所从采用的架构不同时，射频前端通道101所包括的器件/模块不同，具体示例可以参考图6或图8等。
本振电路102，用于产生本振信号。例如，本振电路102可以包括锁相环。
与射频前端通道101和本振电路102耦合的混频电路103，用于根据该本振信号对该宽带射频信号进行下变频操作，以得到基带信号。可以理解的是，基带信号中包含的第一载波的信号频率成分和第二载波的信号频率成分改变，但是，第一载波的信号带宽和第二载波的信号带宽可以不变。也就是说，基带信号的带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。
与混频电路103耦合的滤波器104，用于对该基带信号进行滤波操作，以得到经滤波的信号。该经滤波的信号的带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。滤除操作有助于减少在后续执行模数转换操作时，因混叠特性导致有用信号的信噪比恶化。另外，滤波器104还可以用于调节信号的幅值，使得输出的信号的强度达到预设强度。
本申请实施例提供的无线通信装置，对“带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽”的宽带射频信号进行下变频操作和滤波操作之后，所得到的信号的带宽中仍包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。这样，一方面，在执行下变频操作时，基于一个本振信号，可以得到待执行滤波操作的基带信号。另一方面，在执行滤波操作时，对所生成的一路基带信号进行滤波即可。
而现有技术中，对上述带宽射频信号进行下变频操作和滤波操作之后，分别得到带宽中包含第一载波的信号带宽的信号，和带宽中包含第二载波的信号带宽的信号。基于此，在执行下变频操作时，本振电路至少需要基于第一载波的频率生成一个本振 信号，且基于第二载波的频率生成另一个本振信号。在执行滤波操作时，需要分别对基于这两个本振信号得到的基带信号，进行滤波。
因此，与现有技术相比，本申请实施例提供的无线通信装置，有助于减少本振信号的数量，其中，不同本振信号的频率不同，并且有助于减少滤波操作的执行次数。从而有助于降低无线通信装置的设计复杂度。另外，在硬件实现上，有助于减少生成本振信号所使用的本振电路的个数和执行滤波操作所使用的滤波器的个数，从而有助于节省硬件资源。
可选的，如图5所示，无线通信装置1还包括：与滤波器104耦合的模数转换器105，用于对经滤波的信号进行模数转换操作，其中，模数转换器105的工作带宽大于或等于经滤波的信号的带宽。
可选的，如图5所示，无线通信装置1还包括：载波分离器106，用于将模数转换操作后得到的数字信号进行分离，得到第一载波的信号和第二载波的信号。
可以理解的是，无线通信装置1还可以包括：在数字域上对第一载波的信号和第二载波的信号进行处理的器件/模块等，具体可以参考现有技术，此处不再赘述。
在一种实现方式中，无线通信装置1可以集成在射频芯片中，或者，一部分集成在射频芯片中，另一部分集成在基带芯片中。例如，射频前端通道101、本振电路102、混频电路103、滤波器104或模数转换器105中的至少一种(如本振电路102和混频电路103)集成在射频芯片中；载波分离器106集成在基带芯片中。
在另一种实现方式中，该无线通信装置1为射频芯片。
在另一种实现方式中，该无线通信装置1为终端。
在另一种实现方式中，该无线通信装置1为网络设备如基站。
可选的，宽带射频信号中除了包含非连续的第一载波和第二载波之外，还可以包含第三载波。第三载波可以与第一载波连续或不连续；或者，与第二载波连续或不连续。当然，第三载波也可以与第一载波连续，或者与第二载波连续。本申请实施例对此不进行限定。
在一种实现方式中，第一载波和第二载波是同一通信制式的载波。该实现方式中，第一载波和第二载波可以在同一频带内，如图3所示。其中，第一载波和第二载波中的其中一个载波可以是图3中的载波CC1，另一个载波可以是图3中的载波CC2。
例如，第一载波和第二载波为LTE系统的非连续载波聚合的两个成员载波，这有助于降低LTE系统中无线通信装置的设计复杂度，并且节省LTE系统中的硬件资源。
又如，第一载波和第二载波为NR系统的非连续载波聚合的两个成员载波，这有助于降低NR系统中无线通信装置的设计复杂度，并且节省NR系统中的硬件资源。可选的，第一载波和第二载波属于毫米波频段，当然不限于此。
在另一种实现方式中，第一载波和第二载波是不同通信制式的载波。
例如，第一载波为LTE系统的载波，第二载波为NR系统的载波，第一载波和第二载波是双连接的两个载波。
可选的，第一载波所在的频带与第二载波所在的频带相同(具体是指编号相同，或者频谱资源相同)。例如，如图4A所示，第一载波可以是图4A中的LTE CC，第二载波可以是图4A中的NR CC。例如，第一载波所在的频带包括频带3，第二载波 所在的频带包括频带n3。又如，第一载波所在的频带包括频带41，第二载波所在的频带包括频带n41。
可选的，第一载波所在的频带与第二载波所在的频带的不同(具体是指编号不同和/或频谱资源不同)，且这两个频带之间没有重叠。例如，第一载波可以是图4B中的LTE CC，第二载波可以是图4B中的NR CC。
可选的，第一载波所在的频带与第二载波所在的频带不同(具体是指编号不同和/或频谱资源不同)，且这两个频带之间有重叠。可选的，第一载波和第二载波中的其中一个所在的频带完全覆盖另一个所在的频带。例如，第一载波所在的频带包括频带42，第二载波所在的频带包括频带n78。如图4C所示，第一载波可以是图4C中的LTE CC，第二载波可以是图4C中的NR CC。又如，第一载波所在的频带包括频带42，第二载波所在的频带包括频带n77。
可选的，第一载波和第二载波的信号带宽的大小可以相等或不相等。
以下，以无线通信装置1采用的架构包括零中频架构或超外差架构为例，对无线通信装置1的具体实现方式进行说明。
如图6所示，为无线通信装置1采用零中频架构时的一种结构示意图。在图6中：
射频前端通道101包括：射频滤波器1011和第一放大器1012。其中，与上述滤波器104不同的是，射频滤波器1011是对宽带射频信号RX_IN进行滤波操作的滤波器，并将经滤波的信号发送给第一放大器1012。第一放大器1012用于对接收到的信号进行放大，并将放大后的信号发送给混频电路103。
本振电路102产生的本振信号的频率标记为f LO。
混频电路103具体用于，对接收到的第一放大器1012发送的信号进行下变频操作，得到基带信号。下文中将该基带信号的虚部标记为IMIX_OUT，实部标记为QMIX_OUT。
基带信号的虚部IMIX_OUT经一个滤波器104处理后得到虚部信号IABB_OUT，基带信号的实部QMIX_OUT经另一个滤波器104处理后得到实部信号QABB_OUT。
虚部信号IABB_OUT经一个模数转换器105处理后得到虚部信号RX_IBB，实部信号QABB_OUT经另一个处理后得到实部信号RX_QBB。
虚部信号RX_IBB经载波分离器106处理后得到第一载波的信号的虚部CC1_IBB，以及第二载波的信号的虚部CC2_IBB。实部信号RX_QBB经载波分离器106处理后得到第一载波的信号的实部CC1_QBB，以及第二载波的信号的实部CC2_QBB。
其中，CC1_IBB和CC1_QBB共同用于表征第一载波的信号(具体是第一载波的数字信号)。CC2_IBB和CC2_QBB共同用于表征第二载波的信号(具体是第二载波的数字信号)。
如图7所示，为图6所示的无线通信装置1的工作过程中各节点的信号的频谱示意图。这里的节点是为了方便描述而定义的，具体是图6中的A、B、C、D1和D2。
节点A处的信号表示射频前端通道101接收到的宽带射频信号RX_IN。该信号RX_IN中包含非连续的CC1和CC2的频率成分。本振信号的频率f LO位于CC1和CC2的中心频率f CC1和f CC1之间。该信号RX_IN经射频滤波器1011、第一放大器1012及混频电路103处理之后，得到节点B处的信号。
节点B处的信号表示经混频电路103的处理后得到的信号。相比节点A处的信号，节点B处的信号的频谱统一减小了f LO。
节点C处的信号表示混频电路103输出的信号经滤波器104和模数转换器105处理后得到的信号。节点B处和节点C处的信号的频谱宽度相同，CC1的中心频率的取值相同，且CC2的中心频率的取值也相同。区别可以包括：节点B处的信号是模拟信号，节点C处的信号是数字信号。
节点D1处的信号表示载波分离器106输出的CC1的信号。节点D2处的信号表示是载波分离器106输出的CC2的信号。载波分离器106的一个具体示例可以参考下文。基于下文中对载波分离器106的具体示例的描述可知，载波分离器106输出的信号的中心频率的取值为0(或者接近0)。
图6中所示的无线通信装置1的结构仅为一种示例，其不对本申请实施例可适用的无线通信装置1的结构构成限定。例如，无线通信装置1还可以包括用于对经模数转换操作得到的数字信号进行处理，并将处理后得到的信号发送给载波分离器106。
可扩展地，如果射频前端通道101接收到的宽带射频信号还包括第三载波，则结合图6所示的无线通信装置1，虚部信号RX_IBB经载波分离器106处理后得到第一载波的信号的虚部，第二载波的信号的虚部和第三载波的信号的虚部；实部信号RX_QBB经载波分离器106处理后得到第一载波的信号的实部、第二载波的信号的实部和第三载波的信号的实部。以此类推，可以得到宽带射频信号包括多个非连续载波时，无线通信装置1的处理过程。
基于本申请实施例提供的技术方案，并结合图6，在无线通信装置1中的器件/模块(如滤波器104和模数转换器105)的工作带宽足够(即大于或等于宽带射频信号所包括的载波的带宽以及载波之间的冗余带宽之和)的情况下，使用一个本振信号，分别用于处理信号的实部和虚部的滤波器104，以及分别用于处理信号的实部和虚部的模数转换器105，可以实现对包含多个非连续载波的频率成分的宽带射频信号进行处理。非连续载波的数量越多时，本申请实施例提供的技术方案的降低无线通信装置的设计复杂度和节省硬件资源的效果就越明显。
如图8所示，为无线通信装置1采用超外差架构时的一种结构示意图。在图8中：
射频前端通道101包括：第二放大器1013、移相器1014、合路器1015、第二混频电路1016、第二本振电路1017和第三放大器1018。该情况下，射频前端通道101主要用于完成宽带射频信号的接收和第一次下变频操作。混频电路103主要用于完成第二次下变频操作。
作为示例，射频前端通道101接收到的宽带射频信号经第二放大器1013进行放大，经放大的每一路信号经过一个移相器1014，进行相位调节。多路经移相器1014的信号经合路器1015合并后被发送到第二混频电路1016。第二混频电路1016用于对接收到的信号进行下变频操作。第二混频电路1016执行下变频操作时，所采用的本振信号是由第二本振电路1017产生的。第三放大器1018用于对第二混频电路1016输出的信号(即中频信号)进行放大，并将放大后的信号发送给混频电路103。
如图9所示，为图8所示的无线通信装置1的工作过程中各个节点的信号的示意图。其中，这里的节点是为了方便描述，而定义的，这些节点具体是指图8中的A、B、 C、D、E1和E2。以下对图9中各节点的信号进行说明：
节点A处的信号表示射频前端通道101接收到的宽带射频信号RX_IN。该信号RX_IN中包含非连续的CC1和CC2的频率成分。f HF表示RX_IN的中心频率。该信号RX_IN经第二混频电路1016处理之后，得到的节点B处的信号。
节点B处的信号表示经第二混频电路1016的处理后得到的信号。相比节点A处的信号，节点B处的信号的频谱统一减小了f HF_LO。f HF_LO大于0。例如，载波聚合信号的中心频率由f HF减小到了f IF。其中，f IF＝f HF-f HF_LO。本申请实施例对如何获取f HF_LO的取值不进行限定，具体可以参考现有技术。
节点C处的信号表示经混频电路103的处理后得到的信号。相比节点B处的信号，节点C处的信号的频谱统一减小了f IF，使得载波聚合信号的中心频率由f IF减小到了0。CC1、CC2的信号的中心频率分别减小到了f CC1-f LO、f CC2-f LO。其中，f HF_LO+f IF＝f LO。
图8中节点D处的信号，可以参考上述图7中所示的节点C的信号。图8中节点E1和节点E2的信号可以参考上述图7中所示的节点D1和节点D2的信号。
图8中的本振电路102、混频电路103、滤波器104、模数转换器105和载波分离器106所执行的功能均可以参考上述图6所示的实施例，此处不再赘述。
作为示例，第二混频电路1016可以被称作高频混频电路，上述混频电路103可以被称作中频混频电路。第二本振电路1017可以被称作高频本振电路，上述本振电路102可以被称作中频本振电路。
以下，说明混频电路103产生的本振信号的具体实现方式：
方案一：混频电路103产生的本振信号的频率取值是基于宽带射频信号中包含的载波的最高中心频率与最低中心频率确定的。
可选的，混频电路103产生的本振信号的频率取值为宽带射频信号中包含的载波的最高中心频率与最低中心频率的中间频率。
以宽带射频信号中包含上述第一载波(标记为CC1)和第二载波(标记为CC2)共2个非连续载波，且第一载波和第二载波的频点分别标记为f CC1、f CC2，混频电路103产生的本振信号的频率取值f LO满足如下公式：
Figure PCTCN2019128483-appb-000002
可扩展的，假设宽带射频信号中包含如下载波的频率成分：CC1、CC2、…CCn，这些载波的中心频率依次为f CC1、f CC2、…f CCn，n是大于或等于2的整数，这些中心频率的大小满足f CC1＜f CC2＜…＜f CCn；那么，混频电路103产生的本振信号的频率取值f LO满足如下公式：
Figure PCTCN2019128483-appb-000003
方案二：混频电路103产生的本振信号的频率取值是基于宽带射频信号的中间频率确定的。
可选的，混频电路103产生的本振信号的频率取值为宽带射频信号的中间频率。
以宽带射频信号中包含上述第一载波(标记为CC1)和第二载波(标记为CC2)共2个非连续载波，且第一载波和第二载波的频点分别标记为f CC1、f CC2，信号带宽分别标记为BW CC1、BW CC2为例，宽带射频信号的带宽BW CA满足公式：
Figure PCTCN2019128483-appb-000004
Figure PCTCN2019128483-appb-000005
由此可知，混频电路103产生的本振信号的频率取值f LO满足如下公式：
Figure PCTCN2019128483-appb-000006
可扩展的，假设宽带射频信号中包含如下载波的频率成分：CC1、CC2、…CCn，这些载波的中心频率依次为f CC1、f CC2、…f CCn，其信号带宽分别为BW CC1、BW CC2、…BW CCn，n是大于或等于2的整数。这些中心频率的大小满足f CC1＜f CC2＜…＜f CCn；那么，混频电路103产生的本振信号的频率取值f LO满足如下公式：
Figure PCTCN2019128483-appb-000007
当宽带射频信号包括的各载波单元的信号带宽相同，即BW CC1＝BW CC2＝…＝BW CCn时，上述方案一和方案二是等效的。
可以理解的是，采用方案一或方案二确定混频电路103产生的本振信号的频率取值时，可能导致滤波器104和模数转换器103的工作带宽不同。以下进行具体说明：
其中，滤波器104和模数转换器103的工作带宽可以相等或不相等。在具体实现时，一般将二者设计为相等，下文基于二者相等为例进行说明。滤波器104和模数转换器103的工作带宽的设计原则，是满足信号无损传输。由于滤波器104和模数转换器103处理的是实数信号，因此其带宽特性都是关于零频率对称的，因此：
基于上述方案一，如图10所示可知，BW LFP1可以满足如下公式：
Figure PCTCN2019128483-appb-000008
在图10中，CC1的信号带宽大于CC2的信号带宽。图10中的a图表示图6中的节点A处的信号。图10中的b图表示图6中的节点B处的信号。滤波器104和模数转换器103的工作带宽是BW LFP1。
基于上述方案二，如图11所示可知，滤波器104和模数转换器103的工作带宽BW LFP2可以满足如下公式：
Figure PCTCN2019128483-appb-000009
在图11中，CC1的信号带宽大于CC2的信号带宽。图11中的a图表示图6中的节点A处的信号。图11中的b图表示图6中的节点B处的信号。滤波器104和模数转换器103的工作带宽是BW LFP2。
综上可知：当BW CC1＞BW CC2时，BW LPF1＞BW LPF2；当BW CC1＝BW CC2时，BW LPF1＝BW LPF2。因此，在实际应用中，通过合理选择确定本振信号的频率取值的方案，如当BW CC1＞BW CC2时，选择上述方案二确定本振信号的频率取值，有助于降低滤波器104和模数转换器103的工作带宽，从而有助于降低无线通信装置的功耗。
本申请实施例对载波分离器106的具体实现方式不进行限定。如图11所示，为可适用于本申请实施例的一种载波分离器106的结构示意图。
参见图12，载波分离器106包括：第一数字变频器201、第二数字变频器202、第一采样频率变换器(sample rate converter，SRC)203和第二SRC204。为了便于描述，以下基于图6对载波分离器106中的各器件/模块的功能进行说明。
第一数字变频器201，用于改变图6中的节点C处的信号的频率，以使得该信号中第一载波的信号的搬移到基带，然后将改变频率后的信号发送给与第一数字变频器201连接的第一SRC202。
第一SRC202，用于将所接收到的信号的采样率降低到第一载波所需要的采样率 (该采样率可以是预定义的)，并在降低采样率的过程中，滤除其他载波(如第二载波等)，以及载波间的冗余频率成分，得到第一载波的信号(具体是数字信号)。
第二数字变频器203，用于改变图6中的节点C的频率，以使得该信号中第二载波的信号的搬移到基带，然后将改变频率后的信号发送给与第二数字变频器203连接的第二SRC204。
第二SRC204，用于将所接收到的信号的采样率降低到第二载波所需要的采样率(该采样率可以是预定义的)，并在降低采样率的过程中，将滤除第一载波，以及介于第一载波和第二载波的冗余频率成分，得到第二载波的信号(具体是数字信号)。
作为示例，一个数字变频器可完成一个载波对应的数字信号的搬移。经数字变频器后，期望的载波被搬移到基带，但是仍然保留了其他载波以及无用的频率成分。由于数字变频器仍然是对模数转换器105输出的所有非连续聚合的载波进行操作，因此并没有改变信号的采样率。因此，在数字变频器之后，需要引入SRC202进行降采样率处理，并在降采样操作过程中，将期望载波之外的其他成分滤除。
如图13所示，为图12所示的载波分离器106中各节点的信号的示意图。其中，图12中的节点是基于图7进行绘制的。也就是说，图12中的节点C、节点D1和节点D2处的信号，分别与图7中的节点C、节点D1和节点D2处的信号对应相同。
为了更清楚地描述载波分离器106的工作原理，图12中标记出了节点E1、E2，图13中示意出了节点E1、E2处的信号。
节点E1处的信号是节点C的信号的频谱统一减小f CC1-f LO，以使得载波CC1的中心频率降低为0。该情况下，载波CC2的中心频率为f CC2-f  CC1。节点D1处的信号是滤除节点E1处的信号中的第二载波，以及介于第一载波与第二载波之间的冗余载波之后得到的第一载波的信号。
节点E2处的信号是节点C的信号的频谱统一减小f CC2-f LO，以使得载波CC2的中心频率降低为0。该情况下，载波CC1的中心频率为f CC1-f  CC2。节点D2处的信号是滤除节点E2处的信号中的第一载波，以及介于第一载波与第二载波之间的冗余载波之后得到的第二载波的信号。
在一种实现方式中，如图14所示，第一数字变频器201包括：
第一数控振荡器(numerical controlled oscillator，NCO)2011，用于产生本振信号NCO1，其中，NCO1是由一组相互正交的单音信号NCOI/NCOQ(例如，NCOI是余弦信号，NCOQ就是于正弦信号。这两个信号的相位相差了90度)。该组NCOI/NCOQ的频率是模数转换器105输出的第一载波的中心频率。根据图12可知，NCO1产生的数字本振信号频率为f NCO1＝f CC1-f LO。
复数乘法器2012，用于通过数字本振信号NCO1，与模数转换器105输出的数字信号进行复数乘法操作。按照前述原则设定数字本振信号的频率，即可将第一载波分别搬移到基带。
第二数字变频器203包括：
第二数控振荡器2031，用于产生本振信号NCO2，其中，NCO2是由一组相互正交的单音信号。该组NCOI/NCOQ的频率是模数转换器105输出的第二载波的中心频率。根据图12可知，NCO2产生的数字本振信号频率为f NCO2＝f CC2-f LO。
复数乘法器2032，用于通过数字本振信号NCO2，与模数转换器105输出的数字信号进行复数乘法操作。按照前述原则设定数字本振信号的频率，即可将第二载波分别搬移到基带。
数字信号中，信号的奈奎斯特频率是信号采样率的一半。根据奈奎斯特采样定律，模数转换器105的数据采样率f s需满足：f s＞2×BW LPF。模数转换器105输出的信号的奈奎斯特频率f NC需满足：f NC＞BW LPF。由于载波分离器106输出的是各个独立的载波上的信号，带宽分别为BW CC1和BW CC2，因此，以非连续聚合的载波包括第一载波和第二载波为例，载波分离器106输出的是第一载波和第二载波的信号的奈奎斯特频率需要满足：
Figure PCTCN2019128483-appb-000010
由于信号的频谱带宽越大，需要的奈奎斯特频率越高，同时处理电路需要的功耗等代价也会越大。结合上述分析可知，使用载波分离器106进行载波分离操作之后，需要的奈奎斯特频率也降低了，有助于降低信号处理的代价。另外，载波分离器106中的各个载波输出节点上，由于处理的信号是各独立的载波，且各载波带宽小于模数转换器105输出的信号的总带宽，因此载波分离器106的各载波输出节点上的采样率小于模数转换器105输出节点信号的采样率。
需要说明的是，载波分离器106将输入无线通信装置1的非连续聚合的多个载波，分离成多个独立的载波。图11～图13中以两个载波单元为例，说明了载波分离器106的工作原理。对于更多载波非连续聚合的场景，可依此进行扩展。
如图15所示，为本申请实施例提供的一种信号处理方法的流程示意图，应用于无线通信装置，该方法可以包括：
S101：无线通信装置接收宽带射频信号，宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分。
S102：无线通信装置产生本振信号。
S103：无线通信装置根据该本振信号对该宽带射频信号进行下变频操作，以得到基带信号。
S104：无线通信装置对该基带信号进行滤波操作，以得到经滤波的信号。该经滤波的信号的带宽中包含第一载波的信号带宽，第二载波的信号带宽，以及介于第一载波和第二载波之间的冗余带宽。
S105：无线通信装置对该经滤波的信号进行模数转换操作，其中，执行模数转换操作时所使用模数转换器的工作带宽大于或等于经滤波的信号的带宽。
S106：无线通信装置将模数转换操作后得到的数字信号进行分离，得到第一载波的信号和第二载波的信号。
上述S105和S106是可选的步骤。
关于无线通信装置的具体实现方式，第一载波和第二载波的具体实现方式，本振信号的频率的具体实现方式等，以及该方法能够带来的有益效果等均可以参考上文，此处不再赘述。
在上述实施例中，可以全部或部分地通过软件、硬件、固件或者其任意组合来实现。当使用软件程序实现时，可以全部或部分地以计算机程序产品的形式来实现。该计算机程序产品包括一个或多个计算机指令。在计算机上加载和执行计算机执行指令时，全部或部分地产生按照本申请实施例的流程或功能。计算机可以是通用计算机、 专用计算机、计算机网络、或者其他可编程装置。计算机指令可以存储在计算机可读存储介质中，或者从一个计算机可读存储介质向另一个计算机可读存储介质传输，例如，计算机指令可以从一个网站站点、计算机、服务器或者数据中心通过有线(例如同轴电缆、光纤、数字用户线(digital subscriber line，DSL))或无线(例如红外、无线、微波等)方式向另一个网站站点、计算机、服务器或数据中心进行传输。计算机可读存储介质可以是计算机能够存取的任何可用介质或者是包含一个或多个可以用介质集成的服务器、数据中心等数据存储设备。可用介质可以是磁性介质(例如，软盘、硬盘、磁带)，光介质(例如，DVD)、或者半导体介质(例如固态硬盘(solid state disk，SSD))等。
尽管在此结合各实施例对本申请进行了描述，然而，在实施所要求保护的本申请过程中，本领域技术人员通过查看附图、公开内容、以及所附权利要求书，可理解并实现公开实施例的其他变化。在权利要求中，“包括”(comprising)一词不排除其他组成部分或步骤，“一”或“一个”不排除多个的情况。单个处理器或其他单元可以实现权利要求中列举的若干项功能。相互不同的从属权利要求中记载了某些措施，但这并不表示这些措施不能组合起来产生良好的效果。
尽管结合具体特征及其实施例对本申请进行了描述，显而易见的，在不脱离本申请的精神和范围的情况下，可对其进行各种修改和组合。相应地，本说明书和附图仅仅是所附权利要求所界定的本申请的示例性说明，且视为已覆盖本申请范围内的任意和所有修改、变化、组合或等同物。显然，本领域的技术人员可以对本申请进行各种改动和变型而不脱离本申请的精神和范围。这样，倘若本申请的这些修改和变型属于本申请权利要求及其等同技术的范围之内，则本申请也意图包含这些改动和变型在内。

Claims (30)

  1. 一种无线通信装置，其特征在于，包括：
    射频前端通道，用于接收宽带射频信号，所述宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分；
    本振电路，用于产生本振信号；
    与所述射频前端通道和所述本振电路耦合的混频电路，用于根据所述本振信号对所述宽带射频信号进行下变频操作，以得到基带信号；
    与所述混频电路耦合的滤波器，用于对所述基带信号进行滤波操作，以得到经滤波的信号；所述经滤波的信号的带宽中包含所述第一载波的信号带宽，所述第二载波的信号带宽，以及介于所述第一载波和所述第二载波之间的冗余带宽。
  2. 根据权利要求1所述的无线通信装置，其特征在于：
    所述第一载波和所述第二载波为长期演进系统的非连续载波聚合的两个成员载波。
  3. 根据权利要求1所述的无线通信装置，其特征在于：
    所述第一载波和所述第二载波为新无线电系统的非连续载波聚合的两个成员载波。
  4. 根据权利要求3所述的无线通信装置，其特征在于：
    所述第一载波和所述第二载波属于毫米波频段。
  5. 根据权利要求2至4任一项所述的无线通信装置，其特征在于：
    所述第一载波和所述第二载波在同一频带内。
  6. 根据权利要求1所述的无线通信装置，其特征在于：
    所述第一载波为长期演进系统的载波，所述第二载波为新无线电系统的载波，所述第一载波和所述第二载波是双连接的两个载波。
  7. 根据权利要求6所述的无线通信装置，其特征在于：
    所述第一载波所在的频带与所述第二载波所在的频带相同。
  8. 根据权利要求7所述的无线通信装置，其特征在于：
    所述第一载波所在的频带包括频带3，所述第二载波所在的频带包括频带n3；
    或者，所述第一载波所在的频带包括频带41，所述第二载波所在的频带包括频带n41。
  9. 根据权利要求6所述的无线通信装置，其特征在于：
    所述第一载波所在的频带与所述第二载波所在的频带不相同，但有重叠。
  10. 根据权利要求9所述的无线通信装置，其特征在于：
    所述第一载波所在的频带包括频带42，所述第二载波所在的频带包括频带n77；
    或者，所述第一载波所在的频带包括频带42，所述第二载波所在的频带包括频带n78。
  11. 根据权利要求1至10中任一项所述的无线通信装置，其特征在于：
    所述本振信号的频率取值为所述宽带射频信号中包含的载波的最高中心频率与最低中心频率的中间频率；
    或者，所述本振信号的频率取值为所述宽带射频信号的中间频率。
  12. 根据权利要求1至10中任一项所述的无线通信装置，其特征在于，所述无线通信装置还包括：
    与所述滤波器耦合的模数转换器，用于对所述经滤波的信号进行模数转换操作，其中，所述模数转换器的工作带宽大于或等于所述经滤波的信号的带宽。
  13. 根据权利要求12所述的无线通信装置，其特征在于，所述无线通信装置还包括：
    载波分离器，用于将模数转换操作后得到的数字信号进行分离，得到所述第一载波的信号和所述第二载波的信号。
  14. 根据权利要求13所述的无线通信装置，其特征在于：
    所述本振电路和所述混频电路集成在射频芯片中，所述载波分离器集成在基带芯片中。
  15. 根据权利要求1至13中任一项所述的无线通信装置，其特征在于：
    所述无线通信装置集成在射频芯片中。
  16. 一种信号处理方法，其特征在于，应用于无线通信装置，所述方法包括：
    接收宽带射频信号，所述宽带射频信号中包含非连续的第一载波和第二载波的信号频率成分；
    产生本振信号；
    根据所述本振信号对所述宽带射频信号进行下变频操作，以得到基带信号；
    对所述基带信号进行滤波操作，以得到经滤波的信号；所述经滤波的信号的带宽中包含所述第一载波的信号带宽，所述第二载波的信号带宽，以及介于所述第一载波和所述第二载波之间的冗余带宽。
  17. 根据权利要求16所述的方法，其特征在于：
    所述第一载波和所述第二载波为长期演进系统的非连续载波聚合的两个成员载波。
  18. 根据权利要求17所述的方法，其特征在于：
    所述第一载波和所述第二载波为新无线电系统的非连续载波聚合的两个成员载波。
  19. 根据权利要求18所述的方法，其特征在于：
    所述第一载波和所述第二载波属于毫米波频段。
  20. 根据权利要求16至19任一项所述的方法，其特征在于：
    所述第一载波和所述第二载波在同一频带内。
  21. 根据权利要求16所述的方法，其特征在于：
    所述第一载波为长期演进系统的载波，所述第二载波为新无线电系统的载波，所述第一载波和所述第二载波是双连接的两个载波。
  22. 根据权利要求21所述的方法，其特征在于：
    所述第一载波所在的频带与所述第二载波所在的频带相同。
  23. 根据权利要求22所述的方法，其特征在于：
    所述第一载波所在的频带包括频带3，所述第二载波所在的频带包括频带n3；
    或者，所述第一载波所在的频带包括频带41，所述第二载波所在的频带包括频带n41。
  24. 根据权利要求21所述的方法，其特征在于：
    所述第一载波所在的频带与所述第二载波所在的频带不相同，但有重叠。
  25. 根据权利要求24所述的方法，其特征在于：
    所述第一载波所在的频带包括频带42，所述第二载波所在的频带包括频带n77；
    或者，所述第一载波所在的频带包括频带42，所述第二载波所在的频带包括频带n78。
  26. 根据权利要求16至25中任一项所述的方法，其特征在于：
    所述本振信号的频率取值为所述宽带射频信号中包含的载波的最高中心频率与最低中心频率的中间频率；
    或者，所述本振信号的频率取值为所述宽带射频信号的中间频率。
  27. 根据权利要求16至26中任一项所述的方法，其特征在于，所述方法还包括：
    对所述经滤波的信号进行模数转换操作，其中，执行所述模数转换操作时所使用的模数转换器的工作带宽大于或等于所述经滤波的信号的带宽。
  28. 根据权利要求27所述的方法，其特征在于，所述方法还包括：
    将模数转换操作后得到的数字信号进行分离，得到所述第一载波的信号和所述第二载波的信号。
  29. 一种信号处理装置，其特征在于，包括：存储器和处理器，所述存储器用于存储计算机程序，所述处理器用于调用所述计算机程序，以执行权利要求16至28任一项所述的方法。
  30. 一种计算机可读存储介质，其特征在于，用于存储计算机程序，当所述计算机程序被计算机调用时，使得所述计算机执行权利要求16至28任一项所述的方法。
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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115801144A (zh) * 2022-12-30 2023-03-14 成都富元辰科技有限公司 一种被动侦察系统

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101552765A (zh) * 2009-05-20 2009-10-07 北京数码视讯科技股份有限公司 用于有线数字电视的qam调制器及其载波生成电路
US9473180B2 (en) * 2014-11-20 2016-10-18 Electronics And Telecommunications Research Instit Apparatus for converting frequency and RF transmitter comprising same
CN107040311A (zh) * 2017-04-19 2017-08-11 广东科学技术职业学院 一种自零差相干探测的双向光子射频传输系统及其信号处理实现方法
CN109120278A (zh) * 2017-06-22 2019-01-01 华为技术有限公司 一种载波聚合射频接收机及接收方法

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB201119887D0 (en) * 2011-10-17 2011-12-28 Renesas Mobile Corp Methods of receiving and receivers
GB201119888D0 (en) * 2011-11-17 2011-12-28 Renesas Mobile Corp Methods of receiving and receivers
US9300337B2 (en) * 2013-12-20 2016-03-29 Qualcomm Incorporated Reconfigurable carrier-aggregation receiver and filter
US9634702B2 (en) * 2015-04-30 2017-04-25 Nokia Technologies Oy Multiband filter for non-contiguous channel aggregation
CN109220278A (zh) * 2017-06-04 2019-01-18 张立泉 一种果树嫁接方法
JP7189684B2 (ja) * 2018-05-28 2022-12-14 株式会社アドバンテスト フロントエンド回路、テストボード、テストシステム、コンピュータおよびプログラム

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101552765A (zh) * 2009-05-20 2009-10-07 北京数码视讯科技股份有限公司 用于有线数字电视的qam调制器及其载波生成电路
US9473180B2 (en) * 2014-11-20 2016-10-18 Electronics And Telecommunications Research Instit Apparatus for converting frequency and RF transmitter comprising same
CN107040311A (zh) * 2017-04-19 2017-08-11 广东科学技术职业学院 一种自零差相干探测的双向光子射频传输系统及其信号处理实现方法
CN109120278A (zh) * 2017-06-22 2019-01-01 华为技术有限公司 一种载波聚合射频接收机及接收方法

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115801144A (zh) * 2022-12-30 2023-03-14 成都富元辰科技有限公司 一种被动侦察系统

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