WO2021120397A1 - 一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构 - Google Patents

一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构 Download PDF

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WO2021120397A1
WO2021120397A1 PCT/CN2020/077275 CN2020077275W WO2021120397A1 WO 2021120397 A1 WO2021120397 A1 WO 2021120397A1 CN 2020077275 W CN2020077275 W CN 2020077275W WO 2021120397 A1 WO2021120397 A1 WO 2021120397A1
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stator
rotor
armature winding
teeth
phase
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PCT/CN2020/077275
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English (en)
French (fr)
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贾少锋
冯帅
梁得亮
董晓壮
诸自强
刘进军
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西安交通大学
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K1/00—Details of the magnetic circuit
    • H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
    • H02K1/12—Stationary parts of the magnetic circuit
    • H02K1/14—Stator cores with salient poles
    • H02K1/146—Stator cores with salient poles consisting of a generally annular yoke with salient poles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K1/00—Details of the magnetic circuit
    • H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
    • H02K1/22—Rotating parts of the magnetic circuit
    • H02K1/24—Rotor cores with salient poles ; Variable reluctance rotors
    • H02K1/246—Variable reluctance rotors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K3/00—Details of windings
    • H02K3/04—Windings characterised by the conductor shape, form or construction, e.g. with bar conductors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K2213/00—Specific aspects, not otherwise provided for and not covered by codes H02K2201/00 - H02K2211/00
    • H02K2213/03—Machines characterised by numerical values, ranges, mathematical expressions or similar information

Definitions

  • the invention belongs to the field of motors, and particularly relates to a stator-rotor double-armature winding multiple electromagnetic torque single-air-gap reluctance motor structure.
  • the purpose of the present invention is to overcome the above shortcomings and provide a stator and rotor double armature winding multiple electromagnetic torque single air gap reluctance motor structure.
  • the two sets of windings are superimposed to output mechanical torque, which further increases the torque density, and can also generate torque when any set of windings fails, which improves the fault tolerance of the motor.
  • a stator-rotor double-armature winding multiple electromagnetic torque single-air-gap reluctance motor structure comprising a stator and a rotor with salient pole structures, the rotor is sleeved on the outer circumference of the stator, and there is an air gap between the stator and the rotor;
  • the rotor includes a rotor core and a rotor armature winding, the rotor core includes protruding rotor teeth and a rotor yoke, and the rotor armature winding is wound on the rotor teeth with a structure of fractional slot concentrated winding;
  • the stator includes a stator iron core and a stator armature winding.
  • the stator iron core includes protruding stator teeth and a stator yoke.
  • the stator armature winding adopts a three-phase symmetrical winding structure to be wound on the stator teeth.
  • the rotor armature winding is a two-phase winding, which is fed with a composite current of alternating and superimposed DC components, and the composite current is sequentially fed into the rotor armature winding in the order of i A+ , i B+ , i A- , and i B-; the stator armature Three-phase symmetrical current is passed into the windings, and the stator armature windings are passed into the stator armature windings in the order of i D , i E , and i F.
  • I ac is the effective value of the AC component of the rotor
  • I dc is the average value of the DC component
  • w e is the electrical angular frequency of the rotor armature winding
  • ieri is the initial phase angle of the rotor
  • I acs is the effective value of the stator current
  • w es is The electrical angular frequency of the stator armature winding
  • ieri s is the initial phase angle of the stator
  • N s is the number of stator slots
  • P as is the number of pole pairs of the stator armature winding
  • w r is the mechanical angular velocity.
  • the rotating magnetomotive force of the number of pole pairs P dc generated by the DC component of the rotor armature winding is modulated by the magnetic conductive wave formed by the stator teeth with the number of teeth N s , and the generated rotating excitation magnetic field is exchanged with the rotor armature winding
  • the fundamental magnetomotive force of the pole pair number P ierir generated by the component satisfies the relationship:
  • stator slots N s and the number of rotor slots N r satisfy the formula:
  • k 1 and k 2 are integers
  • m s is the number of AC phases of the stator armature winding
  • m r is the number of AC phases of the rotor armature winding.
  • the outer contours of the rotor teeth and the rotor yoke are all concentric arc structures
  • stator teeth and stator yoke are all concentric arc structures
  • the air gap is formed between the outer contours of the rotor teeth and the stator teeth.
  • the rotor armature winding is a two-phase winding, and two adjacent rotor armature windings are connected to form A+ phase, A-phase, B+ phase and B-phase in sequence.
  • stator armature windings are three-phase windings, and the stator armature windings are sequentially connected to form D phase, E phase, and F phase.
  • the invention has a double salient pole structure, adopts the principle of magnetic field modulation, has strong robustness and high torque density.
  • the stator iron core groove and the rotor iron core groove are both provided with windings, the rotor armature windings are supplied with a DC part and an AC part, and the stator armature windings are supplied with a three-phase alternating current.
  • the two sets of windings work at the same time to output mechanical torque superimposition, which further improves the torque density, and can also generate torque when any set of windings fails, which improves the fault tolerance of the motor.
  • the motor of the invention has high torque density, strong fault tolerance, and can realize multi-mode operation.
  • the stator and rotor armature windings are supplied with power at the same time to achieve high torque density and high efficiency output.
  • the power supply of the fault winding is cut off, and the torque can still be generated.
  • the rotor armature winding fails, the rotor armature winding is cut off for power supply, and the healthy phase winding current is reconstructed.
  • the motor operates as a synchronous reluctance motor to achieve short-term full-load operation; when the stator armature winding fails, the stator armature is removed Winding power supply, the motor is equivalent to a DC bias vernier reluctance motor running, realizing short-term full-load operation.
  • Double armature windings, multiple electromagnetic torques, single stator and single rotor reluctance motors, can determine the number of slots in the stator and rotor of the motor and the armature of the stator and rotor.
  • the matching selection of the number of winding pole pairs and the number of slots enables the motor to contain multiple electromagnetic torque components during normal operation, and has a very high torque density.
  • the full-load output can be realized by reconstructing or increasing the current configuration of the healthy windings, ensuring sufficient fault tolerance.
  • the invention will have broad application prospects in applications including but not limited to vehicle in-wheel motor drive systems, aerospace, deep-sea exploration, etc., which require motors with high torque density and high fault tolerance.
  • Figure 1 is a schematic diagram of the structure of the present invention
  • Figure 2 is a schematic diagram of the rotor winding connection
  • Figure 3 is a schematic diagram of the stator winding connection.
  • the invention provides a stator-rotor double-armature winding multiple electromagnetic torque single-air-gap reluctance motor structure including a stator and a rotor, and the stator and rotor cores are both salient pole structures. There is an air gap between the stator and the rotor, and the rotor includes a rotor iron.
  • the stator includes the stator iron core and the stator armature winding, the stator iron core faces The outer protrusions form stator teeth, and the stator armature winding adopts a three-phase symmetric winding structure to be wound on the stator teeth.
  • stator and rotor proposed by the present invention are relative, and are finally determined according to actual application occasions and system cost considerations.
  • the composite current is fed into the rotor armature winding in the order of i A+ , i B+ , i A- , i B- ; the stator armature winding is fed with three-phase symmetrical current, and in accordance with The order of i D , i E , i F is connected to the stator armature winding in turn.
  • the rotor armature winding is a two-phase winding, and a composite current of alternating and superimposed DC components is passed through feasible devices such as brush slip rings and resolvers.
  • the expression of each phase current is:
  • I ac is the effective value of the AC component of the rotor
  • I dc is the average value of the DC component
  • w e is the electrical angular frequency of the rotor armature winding
  • ieri is the initial phase angle of the rotor
  • I acs is the effective value of the stator current
  • w es is The electrical angular frequency of the stator armature winding
  • ieri s is the initial phase angle of the stator
  • N s is the number of stator slots
  • P as is the number of pole pairs of the stator armature winding
  • w r is the mechanical angular velocity.
  • the rotating magnetomotive force with the number of pole pairs P dc generated by the DC component of the rotor armature winding is modulated by the magnetic conductive wave formed by the stator teeth with the number of teeth N s , and the resulting rotating excitation magnetic field is exchanged with the rotor armature winding
  • the fundamental magnetomotive force whose number of pole pairs generated by the component is P ierir satisfies the relationship:
  • the number of pole pairs of the stator armature winding is P as . After the alternating current is applied, the stator rotating magnetic potential of the poles of P as is formed. When the pole pair number of the unmodulated DC rotating magnetic field generated by the rotor DC component is the same, the following is satisfied When formulating the formula, the stator electromagnetic torque will be generated.
  • stator electromagnetic torque After the stator winding is energized with alternating current, the P as counter-pole stator rotating magnetic potential is formed. After the magnetic conductive wave formed by the stator teeth with the number of teeth N s is magnetically modulated, the generated rotating magnetic field and the rotating magnetic field generated by the AC component of the rotor The same logarithm, that is, when the following formula is satisfied, stator electromagnetic torque will be generated.
  • the second is the electromagnetic torque produced by the unmodulated DC rotating magnetic field of the rotor armature winding and the alternating current of the stator armature winding;
  • the third is the reluctance torque formed by the alternating current of the stator armature winding and the salient poles of the rotor Component;
  • the rotating magnetomotive force generated by the AC component of the stator armature winding interacts with the rotating magnetic field generated by the AC component of the rotor to generate torque after being modulated by the stator teeth.
  • stator and rotor slots meet the formula:
  • k 1 and k 2 are integers
  • m s is the number of AC phases of the stator armature winding
  • m r is the number of AC phases of the rotor armature winding.
  • the present invention includes a stator 4, a rotor 2, an air gap 3 between the stator 4 and the rotor 2, the rotor 2 includes rotor teeth 2-1 and the rotor armature winding 1, the stator 4 includes stator teeth 4-1 and stator electrical
  • the pivot winding 5, the rotor armature winding 1 are wound on the rotor teeth 2-1 in a fractional slot concentrated winding structure, and the stator armature winding 5 is wound on the stator teeth 4-1 in a three-phase symmetrical winding structure.
  • the composite current flows into the rotor armature windings in the order of i A+ , i B+ , i A- , and i B- ; the stator armature windings are fed with three-phase symmetrical currents in the order of i D , i E , and i F Pass into the stator armature winding.
  • the rotor armature winding is a two-phase winding, and a composite current of alternating and superimposed DC components is passed through feasible devices such as brush slip rings and resolvers.
  • the expression of each phase current is:
  • I ac is the effective value of the rotor AC component
  • I dc is the average value of the DC component
  • w e is the rotor electrical angular frequency
  • ieri is the rotor initial phase angle
  • I acs is the effective value of the stator current
  • w es is the stator electrical angle Frequency
  • ieri s is the initial phase angle of the stator
  • N s is the number of stator slots
  • P as is the number of pole pairs of the stator armature winding
  • w r is the mechanical angular velocity.
  • the stator and rotating slot poles of the motor of the present invention are matched at 9/8.
  • the DC component in the rotor armature winding generates 4 pairs of pole rotating magnetomotive force
  • the AC component generates 5 pairs of pole rotating magnetomotive force
  • the stator armature winding generates 4 pairs of pole rotation. Magnetomotive force.
  • the 5-pole rotating magnetic field generated is coupled with the rotor AC component magnetic field to produce the first part of the torque component; the rotor armature winding DC component is not
  • the 4-pair-pole rotating magnetomotive force generated by modulation is coupled with the 4-pair-pole rotating magnetic field generated by the AC component of the stator armature winding to produce the second part of the torque component; the third part is formed by the AC component of the stator armature winding and the salient poles of the rotor.
  • the rotor armature winding is a two-phase winding, and two adjacent rotor armature windings are connected to form A+ phase, A- phase, B+ phase and B- phase in sequence.
  • the stator armature windings are three-phase windings, and the stator armature windings are sequentially connected to form D phase, E phase, and F phase.
  • the motor is equivalent to an 8-pole synchronous reluctance motor to achieve short-term full-load operation; when the stator armature winding fails, the stator power is removed Pivot winding power supply, the motor is equivalent to the operation of a 2-phase DC bias vernier reluctance motor, realizing short-term full-load operation. Therefore, the new motor has strong fault tolerance and strong robustness.
  • the invention improves the structure of the motor and adds double armature windings to generate multiple electromagnetic torques.
  • the stator or rotor armature windings fail, the healthy phase current can be reconstructed to still realize short-term full-load operation, thus realizing the motor High torque density and high fault tolerance.
  • the stator and rotor cores of the motor adopt salient pole structures, and the motor model is relatively simple, easy to process, and robust.
  • the invention will have a wide application prospect in the application occasions of high torque density and high fault tolerance.

Abstract

本发明公开了一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，包括均为凸极结构的定子和转子，转子套设在定子外周，定子与转子间具有气隙；所述转子包括转子铁芯和转子电枢绕组，转子铁芯向内凸出形成转子齿，转子电枢绕组采用分数槽集中绕组的结构缠绕在转子齿上；所述定子包括定子铁芯和定子电枢绕组，定子铁芯向外凸出形成定子齿，定子电枢绕组采用三相对称绕组结构缠绕在定子齿上。正常工作时，两套绕组叠加，输出机械转矩，进一步提高了转矩密度，并且在任意一套绕组故障时也能产生转矩，提高了电机的容错能力。

Description

一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构 技术领域
本发明属于电机领域，具体涉及一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构。
背景技术
近年来，随着节能与排放的双重压力，新能源汽车已成为未来电动汽车的重要发展方向。作为新能源汽车的核心动力部件，要求新能源汽车用电机必须具有高转矩密度(功率密度)、高效率、高容错能力等。永磁电机因转矩密度大、功率因数高，而得到了研究人员广泛的关注。但是永磁材料价格偏高，且存在高温失磁的风险，使得永磁电机成本偏高，且故障率高。传统开关磁阻电机有着结构简单、价格低廉的优点，但存在着噪声、振动和转矩脉动较大的缺陷。近年来，基于磁场调制原理的磁场调制型电机受到了较高的关注，直流偏置游标磁阻电机即为其中的一种，其将直流和交流分量通入到相同的线圈，充分利用导体的通流能力，在相同铜耗时提升了输出转矩。
除此之外，现有大多数类型的电机，如电励磁同步电机、同步磁阻电机、开关磁链、磁通反向电机、永磁电机等都只含有一套电枢绕组，容错性能较差。为提高电机的容错能力，现有的技术方案一般是提高电机定子侧绕组的相数，或者增加定子侧绕组的套数。造成定子空间的冲突以及转子侧空间的浪费。
发明内容
本发明的目的在于克服上述不足，提供一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构。正常工作时，两套绕组叠加，输出机械转矩，进一步 提高了转矩密度，并且在任意一套绕组故障时也能产生转矩，提高了电机的容错能力。
为了达到上述目的，本发明采用如下技术方案：
一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，包括均为凸极结构的定子和转子，转子套设在定子外周，定子与转子间具有气隙；
所述转子包括转子铁芯和转子电枢绕组，转子铁芯包含凸出的转子齿和转子轭部，转子电枢绕组采用分数槽集中绕组的结构缠绕在转子齿上；
所述定子包括定子铁芯和定子电枢绕组，定子铁芯包含凸出的定子齿和定子轭部，定子电枢绕组采用三相对称绕组结构缠绕在定子齿上。
所述转子电枢绕组为两相绕组，通入交流叠加直流分量的复合电流，复合电流按照i A+、i B+、i A-、i B-的顺序依次通入转子电枢绕组；定子电枢绕组通入三相对称电流，并按照i D、i E、i F的顺序依次通入定子电枢绕组。
各相电流表达式为：
Figure PCTCN2020077275-appb-000001
Figure PCTCN2020077275-appb-000002
Figure PCTCN2020077275-appb-000003
Figure PCTCN2020077275-appb-000004
Figure PCTCN2020077275-appb-000005
Figure PCTCN2020077275-appb-000006
Figure PCTCN2020077275-appb-000007
ω e＝N sω r
ω es＝P asω r
其中，I ac为转子交流分量的有效值，I dc为直流分量平均值，w e为转子电枢绕组电角频率，а为转子初相角，I acs为定子电流的有效值，w es为定子电枢绕组电角频率，а s为定子初相角，N s为定子槽数，P as为定子电枢绕组极对数，w r为机械角速度。
所述转子电枢绕组直流分量产生的极对数P dc的旋转磁动势通过齿数N s的定子齿所形成的磁导波进行磁场调制后，产成的旋转励磁磁场与转子电枢绕组交流分量产生的极对数P аr的基波磁动势满足关系：
P ar＝|N s±P dc|   (1)
定子绕组的极对数P as，通入交流电后，形成P as对极的定子旋转磁势，当与转子直流分量产生的未经调制的直流旋转磁场极对数相同，即满足下述公式时，会产生定子电磁转矩；
P dc＝P as  (2)
当转子槽数N r与定子电枢绕组的极对数为P as满足下述公式时，将会产生类似于同步磁阻转矩的磁阻转矩分量；
N r＝2P as  (3)
定子绕组通入交流电后，形成的P as对极的定子旋转磁势，经过齿数N s的定子齿所形成的磁导波进行磁场调制后，产生的旋转磁场与转子交流分量产生的旋转磁场极对数相同，即满足下述公式时，会产生定子电磁转矩，表达式如下：
P ar＝|N s±P as|   (4)。
所述定子槽数N s、转子槽数N r满足公式：
N s＝k 1m s
N r＝k 2m r
式中，k 1、k 2为整数，m s为定子电枢绕组交流相数，m r为转子电枢绕组交流相数。
所述定子、转子的槽数和极对数配合关系为：
Figure PCTCN2020077275-appb-000008
所述转子齿和转子轭部外部轮廓均为同心的圆弧结构；
所述定子齿和定子轭部外部轮廓均为同心的圆弧结构；
所述转子齿和定子齿外部轮廓之间为所述气隙。
所述转子电枢绕组为两相绕组，相邻两个转子电枢绕组连接，依次形成A+相、A-相、B+相和B-相。
所述定子电枢绕组为三相绕组，定子电枢绕组依次连接形成D相、E相、F相。
与现有技术相比，具有以下优点：
本发明为双凸极结构，采用磁场调制原理，鲁棒性强，转矩密度高。定子铁芯凹槽和转子铁芯凹槽中均设置有绕组，转子电枢绕组通入电流包含直流部分和交流部分，定子电枢绕组通入三相交流电。正常工作时，两套绕组同时工作输出机械转矩叠加，进一步提高了转矩密度，并且在任意一套绕组故障时也能产生转矩，提高了电机的容错能力。
本发明电机具有转矩密度高，容错能力强，且能实现多模态运行。在正常运行时，定转子电枢绕组同时供电，实现高转矩密度高效率输出。在电机定子或转子电枢绕组故障时，切除故障绕组供电，仍能产生转矩。当转子电枢绕组故障时，切除转子电枢绕组供电，对健康相绕组电流重构，电机相当于同步磁 阻电机运行，实现短时满载运行；当定子电枢绕组故障时，切除定子电枢绕组供电，电机相当于直流偏置游标磁阻电机运行，实现短时满载运行。
不同于开关磁阻电机、电励磁同步电机等现有电机类型只有一套电枢绕组，双电枢绕组多重电磁转矩单定子单转子磁阻电机通过对电机定转子槽数、定转子电枢绕组极对数槽数的配合选择，使得电机在正常运行时将含有多重电磁转矩分量，具有极高的转矩密度。同时在一套绕组故障时，通过重构或增大健康绕组的电流配置，实现满载输出，保证了足够的容错性能。该发明在包括但不限于车辆轮毂电机驱动系统、航空航天、深海探测等等要求电机具有高转矩密度高容错能力的应用场合将具有广泛的应用前景。
附图说明
图1为本发明的结构示意图；
图2为转子绕组连接示意图；
图3为定子绕组连接示意图。
其中：1、转子电枢绕组；2、转子；2-1、转子齿；3、气隙；4、定子；4-1、定子齿；5、定子电枢绕组。
具体实施方式
本发明一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构包括定子、转子，且定、转子铁芯均为凸极结构，定、转子间具有气隙，转子包括转子铁芯和转子电枢绕组，转子铁芯向内凸出形成转子齿，转子电枢绕组采用分数槽集中绕组的结构缠绕在转子齿上；定子包括定子铁芯和定子电枢绕组，定子铁芯向外凸出形成定子齿，定子电枢绕组采用三相对称绕组结构缠绕在定子齿上。
需要声明的是本发明所提出的定转子是相对的，根据实际应用场合和系统成本考虑最终确定。
作为一种成本较低的实施方案为：复合电流按照i A+、i B+、i A-、i B-的顺序依次通入转子电枢绕组；定子电枢绕组通入三相对称电流，并按照i D、i E、i F的顺序依次通入定子电枢绕组。转子电枢绕组为两相绕组，通过电刷滑环、旋转变压器等可行的装置通入交流叠加直流分量的复合电流，各相电流表达式为：
Figure PCTCN2020077275-appb-000009
Figure PCTCN2020077275-appb-000010
Figure PCTCN2020077275-appb-000011
Figure PCTCN2020077275-appb-000012
Figure PCTCN2020077275-appb-000013
Figure PCTCN2020077275-appb-000014
Figure PCTCN2020077275-appb-000015
ω e＝N sω r
ω es＝P asω r
其中，I ac为转子交流分量的有效值，I dc为直流分量平均值，w e为转子电枢绕组电角频率，а为转子初相角，I acs为定子电流的有效值，w es为定子电枢绕组电角频率，а s为定子初相角，N s为定子槽数，P as为定子电枢绕组极对数，w r为机械角速度。
转子电枢绕组直流分量产生的极对数为P dc的旋转磁动势通过齿数为N s的定子齿所形成的磁导波进行磁场调制后，产成的旋转励磁磁场与转子电枢绕组交流分量产生的极对数为P аr的基波磁动势满足关系：
P ar＝|N s±P dc|
定子电枢绕组的极对数为P as，通入交流电后，形成P as对极的定子旋转磁势，当与转子直流分量产生的未经调制的直流旋转磁场极对数相同，即满足下述公式时，会产生定子电磁转矩。
P dc＝P as
当转子槽数N r与定子电枢绕组的极对数为P as满足下述公式时，将会产生类似于同步磁阻转矩的磁阻转矩分量。
N r＝2P as
定子绕组通入交流电后，形成的P as对极的定子旋转磁势，经过齿数N s的定子齿所形成的磁导波进行磁场调制后，产生的旋转磁场与转子交流分量产生的旋转磁场极对数相同，即满足下述公式时，会产生定子电磁转矩。
P ar＝|N s±P as|
以上分析表明，若电机参数选择合适，将会产生四部分转矩，一是转子电枢绕组直流分量通过定子齿部调制成的旋转磁场与转子电枢绕组交流分量产生的旋转磁场相互作用产生转矩；二是转子电枢绕组直流分量未经调制产生的直流旋转磁场与定子电枢绕组交流量产生的电磁转矩；三是定子电枢绕组交流量与转子凸极所形成的磁阻转矩分量；四是定子电枢绕组交流量产生的旋转磁动势经过定子齿调制后与转子交流分量产生的旋转磁场相互作用产生转矩。当四部分转矩作用于转子的方向相同时，合成的电磁转矩最大。
一种满足上述三个关系的定转子槽数和极对数配合为：
定子槽数N s 转子槽数N r 定子电枢绕组极对数P as 转子电枢绕组极对数P ar 转子直流极对数P dc
9 8 4 5 4
其中，定、转子槽数满足公式：
N s＝k 1m s
N r＝k 2m r
式中，k 1、k 2为整数，m s为定子电枢绕组交流相数，m r为转子电枢绕组交流相数。
而其他满足上述六个公式的所有槽极配合且符合本专利所述原理的，都属于本专利的保护范围内，此处不在列出。此外，本专利以外转子电机模型为例，符合本专利所述原理的包括但不限于内转子电机、轴向磁场电机，都属于本专利的保护范围内。
下面结合附图对本发明做进一步说明。
实施例
参见图1，本发明包括定子4、转子2，定子4与转子2间具有气隙3，转子2包括转子齿2-1和转子电枢绕组1，定子4包括定子齿4-1和定子电枢绕组5，转子电枢绕组1采用分数槽集中绕组的结构缠绕在转子齿2-1上，定子电枢绕组5采用三相对称绕组结构缠绕在定子齿4-1上。
复合电流按照i A+、i B+、i A-、i B-的顺序依次通入转子电枢绕组；定子电枢绕组通入三相对称电流，并按照i D、i E、i F的顺序依次通入定子电枢绕组。转子电枢绕组为两相绕组，通过电刷滑环、旋转变压器等可行的装置通入交流叠加直流分量的复合电流，各相电流表达式为：
Figure PCTCN2020077275-appb-000016
Figure PCTCN2020077275-appb-000017
Figure PCTCN2020077275-appb-000018
Figure PCTCN2020077275-appb-000019
Figure PCTCN2020077275-appb-000020
Figure PCTCN2020077275-appb-000021
Figure PCTCN2020077275-appb-000022
ω e＝N sω r
ω es＝P asω r
其中，I ac为转子交流分量的有效值，I dc为直流分量平均值，w e为转子电角频率，а为转子初相角，I acs为定子电流的有效值，w es为定子电角频率，а s为定子初相角，N s为定子槽数，P as为定子电枢绕组极对数，w r为机械角速度。
为了更好的解释本电机的工作原理，下面结合附图1对本发明进行说明。
本发明电机定、转槽极配合为9/8，转子电枢绕组中直流分量产生4对极旋转磁动势，交流分量产生5对极旋转磁动势，定子电枢绕组产生4对极旋转磁动势。转子电枢绕组直流分量产生的4对极旋转磁动势经过定子齿磁场调制之后，产生的5对极旋转磁场和转子交流分量磁场耦合，产生第一部分转矩分量；转子电枢绕组直流分量未经调制产生的4对极旋转磁动势与定子电枢绕组交流分量产生的4对极旋转磁场耦合，产生第二部分转矩分量；定子电枢绕组交流分量与转子凸极所形成的第三部分磁阻转矩分量；定子电枢绕组产生的4对极旋转磁动势经过定子齿调制后，产生的5对极旋转磁场和转子交流分量产生的5对极旋转磁场耦合，产生第四部分转矩。当四部分转矩作用于转子的方向相同时，合成的电磁转矩最大。
如图2和图3所示，所述转子电枢绕组为两相绕组，相邻两个转子电枢绕组连接，依次形成A+相、A-相、B+相和B-相。所述定子电枢绕组为三相绕组，定子电枢绕组依次连接形成D相、E相、F相。
当转子电枢绕组故障时，切除转子电枢绕组供电，对健康相电流重构，电机相当于8极同步磁阻电机运行，实现短时满载运行；当定子电枢绕组故障时，切除定子电枢绕组供电，电机相当于2相直流偏置游标磁阻电机运行，实现短时满载运行。因此，该新型电机具有较强的容错性能，鲁棒性强。
本发明通过对电机结构改进，加入双电枢绕组，产生多重电磁转矩，并在定子或转子电枢绕组故障时，通过对健康相电流重构，仍能实现短时满载运行，实现了电机高转矩密度和高容错能力。电机定、转子铁芯均采用凸极结构，电机模型相对简单，便于加工，鲁棒性强。本发明在高转矩密度和高容错能力的应用场合将具有广泛的应用前景。
以上，仅为本发明的较佳实施例，并非仅限于本发明的实施范围，凡依本发明专利范围的内容所做的等效变化和修饰，都应为本发明的技术范畴。
本发明的实施方式只是对本专利的示例性说明，并不限定它的保护范围，本领域技术人员还可以对其局部进行改变，只要没超出本专利的精神实质，都在本专利的保护范围内。

Claims (9)

  1. 一种定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，包括均为凸极结构的定子和转子，转子套设在定子外周，定子与转子间具有气隙；
    所述转子包括转子铁芯和转子电枢绕组，转子铁芯包含凸出的转子齿和转子轭部，转子电枢绕组采用分数槽集中绕组的结构缠绕在转子齿上；
    所述定子包括定子铁芯和定子电枢绕组，定子铁芯包含凸出的定子齿和定子轭部，定子电枢绕组采用三相对称绕组结构缠绕在定子齿上。
  2. 根据权利要求1所述的定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，所述转子电枢绕组为两相绕组，通入交流叠加直流分量的复合电流，复合电流按照i A+、i B+、i A-、i B-的顺序依次通入转子电枢绕组；定子电枢绕组通入三相对称电流，并按照i D、i E、i F的顺序依次通入定子电枢绕组。
  3. 根据权利要求2所述的定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，各相电流表达式为：
    Figure PCTCN2020077275-appb-100001
    Figure PCTCN2020077275-appb-100002
    Figure PCTCN2020077275-appb-100003
    Figure PCTCN2020077275-appb-100004
    Figure PCTCN2020077275-appb-100005
    Figure PCTCN2020077275-appb-100006
    Figure PCTCN2020077275-appb-100007
    ω e＝N sω r
    ω es＝P asω r
    其中，I ac为转子交流分量的有效值，I dc为直流分量平均值，w e为转子电枢绕组电角频率，а为转子初相角，I acs为定子电流的有效值，w es为定子电枢绕组电角频率，а s为定子初相角，N s为定子槽数，P as为定子电枢绕组极对数，w r为机械角速度。
  4. 根据权利要求1所述的定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，所述转子电枢绕组直流分量产生的极对数P dc的旋转磁动势通过齿数N s的定子齿所形成的磁导波进行磁场调制后，产成的旋转励磁磁场与转子电枢绕组交流分量产生的极对数P аr的基波磁动势满足关系：
    P ar＝|N s±P dc|  (1)
    定子绕组的极对数P as，通入交流电后，形成P as对极的定子旋转磁势，当与转子直流分量产生的未经调制的直流旋转磁场极对数相同，即满足下述公式时，会产生定子电磁转矩；
    P dc＝P as  (2)
    当转子槽数N r与定子电枢绕组的极对数为P as满足下述公式时，将会产生类似于同步磁阻转矩的磁阻转矩分量；
    N r＝2P as  (3)
    定子绕组通入交流电后，形成的P as对极的定子旋转磁势，经过齿数N s的定子齿所形成的磁导波进行磁场调制后，产生的旋转磁场与转子交流分量产生的旋转磁场极对数相同，即满足下述公式时，会产生定子电磁转矩，表达式如下：
    P ar＝|N s±P as|(4)。
  5. 根据权利要求1所述的定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，所述定子槽数N s、转子槽数N r满足公式：
    N s＝k 1m s
    N r＝k 2m r
    式中，k 1、k 2为整数，m s为定子电枢绕组交流相数，m r为转子电枢绕组交流相数。
  6. 根据权利要求5所述的定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，所述定子、转子的槽数和极对数配合关系为：
    Figure PCTCN2020077275-appb-100008
  7. 根据权利要求1所述的定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，
    所述转子齿和转子轭部外部轮廓均为同心的圆弧结构；
    所述定子齿和定子轭部外部轮廓均为同心的圆弧结构；
    所述转子齿和定子齿外部轮廓之间为所述气隙。
  8. 根据权利要求1所述的定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，所述转子电枢绕组为两相绕组，相邻两个转子电枢绕组连接，依次形成A+相、A-相、B+相和B-相。
  9. 根据权利要求1所述的定转子双电枢绕组多重电磁转矩单气隙磁阻电机结构，其特征在于，所述定子电枢绕组为三相绕组，定子电枢绕组依次连接形成D相、E相、F相。
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