WO2020240916A1 - Multiband antenna - Google Patents

Multiband antenna Download PDF

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Publication number
WO2020240916A1
WO2020240916A1 PCT/JP2020/002036 JP2020002036W WO2020240916A1 WO 2020240916 A1 WO2020240916 A1 WO 2020240916A1 JP 2020002036 W JP2020002036 W JP 2020002036W WO 2020240916 A1 WO2020240916 A1 WO 2020240916A1
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WO
WIPO (PCT)
Prior art keywords
antenna
inductance
frequency
band
high inductance
Prior art date
Application number
PCT/JP2020/002036
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French (fr)
Japanese (ja)
Inventor
渡 野口
Original Assignee
パナソニックＩｐマネジメント株式会社
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Publication of WO2020240916A1 publication Critical patent/WO2020240916A1/en

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/30—Arrangements for providing operation on different wavebands
    • H01Q5/307—Individual or coupled radiating elements, each element being fed in an unspecified way
    • H01Q5/314—Individual or coupled radiating elements, each element being fed in an unspecified way using frequency dependent circuits or components, e.g. trap circuits or capacitors
    • H01Q5/321—Individual or coupled radiating elements, each element being fed in an unspecified way using frequency dependent circuits or components, e.g. trap circuits or capacitors within a radiating element or between connected radiating elements
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/16—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole

Definitions

  • This disclosure relates to a multi-band antenna.
  • wireless terminals based on standards such as wireless LAN (Local Area Network) and Bluetooth (registered trademark) have begun to be installed in home appliances such as televisions and audio equipment. ..
  • wireless communication may be performed in a plurality of frequency bands corresponding to a plurality of standards.
  • a multi-band antenna capable of transmitting and receiving signals in a plurality of frequency bands with one antenna has been proposed (for example, Patent Document 1 and the like). ).
  • the dual band antenna described in Patent Document 1 includes a linear body portion and a helical coil-shaped portion.
  • This helical coil-like portion functions as a choke coil for signals in a high frequency band, and functions as a part of a miniaturized antenna for signals in a low frequency band.
  • Patent Document 1 attempts to realize a dual-band antenna that is compact and can have different effective electrical lengths depending on the frequency.
  • the present disclosure provides a multi-band antenna that resonates in a plurality of frequency bands and can realize directivity perpendicular to the resonance direction in each frequency band.
  • the multi-band antenna includes a substrate, an input terminal arranged on the substrate and input with a signal, and an antenna portion arranged on the substrate and connected to the input terminal.
  • the first low inductance portion connected in series, the first high inductance portion having a meander shape, and the conductive antenna portion having the first tip portion, which are connected in series from the input terminal side, are arranged on the substrate.
  • the first low inductance section has a lower inductance than the first high inductance section
  • the second low inductance section has a lower inductance than the second high inductance section
  • the first low inductance section has a conductive grounding section.
  • the electric length of the low inductance portion is 1/4 wavelength of the first frequency, and the sum of the electrical lengths of the first low inductance portion, the first high inductance portion, and the first tip portion is from the first frequency. It is a quarter wavelength of the lower second frequency.
  • the multi-band antenna it is possible to resonate in a plurality of frequency bands and realize directivity perpendicular to the resonance direction in each frequency band.
  • FIG. 1 is a plan view showing the configuration of the multi-band antenna according to the first embodiment.
  • FIG. 2 is a plan view showing the configuration of the multi-band antenna according to the comparative example.
  • FIG. 3 is a diagram showing an outline of directivity at the first frequency of the multi-band antenna according to the first embodiment.
  • FIG. 4 is a diagram showing an outline of the directivity of the multi-band antenna according to the comparative example at the first frequency.
  • FIG. 5 is a graph showing an example of a simulation result of the directivity of the multi-band antenna according to the first embodiment.
  • FIG. 6 is a graph showing another example of the directivity simulation result of the multi-band antenna according to the first embodiment.
  • FIG. 7 is a graph showing the relationship between the width of the ground contact portion and the minimum inductance value of each high inductance element of the second high inductance portion according to the first embodiment.
  • FIG. 8 is a first plan view showing the configuration of the antenna module according to the second embodiment.
  • FIG. 9 is a second plan view showing the configuration of the antenna module according to the second embodiment.
  • FIG. 10 is a plan view showing the configuration of the three distributors according to the second embodiment.
  • FIG. 11 is a graph showing the directivity of the array antenna according to the second embodiment.
  • FIG. 12 is a graph showing the directivity when the state of the phase shifter of the array antenna according to the second embodiment is changed.
  • FIG. 13 is a perspective view showing the configuration of an audio device including the antenna module according to the second embodiment.
  • FIG. 14 is a plan view showing the configuration of the multi-band antenna according to the third embodiment.
  • FIG. 15 is a graph showing an example of the first simulation result of the directivity of the multi-band antenna according to the third embodiment.
  • FIG. 16 is a graph showing an example of the second simulation result of the directivity of the multi-band antenna according to the third embodiment.
  • FIG. 17 is a graph showing the relationship between the width of the ground contact portion and the minimum inductance value of each high inductance element of the second high inductance portion according to the third embodiment.
  • each figure is a schematic view and is not necessarily exactly illustrated. Further, in each figure, the same components are designated by the same reference numerals.
  • FIG. 1 is a plan view showing the configuration of the multi-band antenna 1 according to the present embodiment.
  • FIG. 1 shows a plan view of the substrate 40 of the multi-band antenna 1 in a plan view.
  • the direction perpendicular to the main surface 41 of the substrate 40 of the multi-band antenna 1 is the Z-axis direction
  • the two directions perpendicular to the Z-axis direction and perpendicular to each other are the X-axis direction and the Y-axis direction. It is said.
  • the multi-band antenna 1 is an antenna that transmits and receives signals in a plurality of frequency bands.
  • the multi-band antenna 1 transmits and receives a signal in the first frequency band including the first frequency and a signal in the second frequency band including the second frequency lower than the first frequency.
  • the first frequency band and the second frequency band are not particularly limited, but in the present embodiment, the 5 GHz band and the 2.4 GHz band are used as the first frequency band and the second frequency band, respectively.
  • the multi-band antenna 1 can be used as a dual-band antenna in the 5 GHz band and the 2.4 GHz band based on the wireless LAN standard.
  • the multi-band antenna 1 includes a substrate 40, an input terminal 16, an antenna portion 10, and a grounding portion 20.
  • the multi-band antenna 1 further includes a ground terminal 26.
  • the substrate 40 is a member that serves as a base for the multi-band antenna 1.
  • the substrate 40 is a circuit board, and the antenna portion 10 and the grounding portion 20 are arranged on one main surface 41 of the substrate 40.
  • the substrate 40 is a rectangular plate-shaped dielectric.
  • the substrate 40 is, for example, a glass epoxy substrate.
  • the input terminal 16 is a terminal arranged on the board 40 to input a signal.
  • the high frequency signal transmitted by the multi-band antenna 1 is input to the input terminal 16.
  • the input terminal 16 also functions as an output terminal that outputs a high-frequency signal received by the multi-band antenna 1.
  • a signal is input to the input terminal 16 from, for example, a main surface on the back side of the main surface 41 of the substrate 40 via a via wiring penetrating the substrate 40. Further, the input terminal 16 is connected to the antenna unit 10.
  • the ground terminal 26 is a terminal arranged on the board 40 and connected to the ground.
  • the ground terminal 26 is arranged on the main surface 41 of the substrate 40 and is connected to the ground portion 20.
  • the ground terminal 26 is connected to the ground via, for example, a via wiring penetrating the substrate 40.
  • the number of ground terminals 26 is not particularly limited, but is two in the present embodiment.
  • the antenna portion 10 is a conductive member arranged on the substrate 40 and connected to the input terminal 16.
  • the signal in the first frequency band and the signal in the second frequency band resonate in the antenna unit 10.
  • radio waves are radiated from the antenna unit 10.
  • the antenna portion 10 has a first low inductance portion 11, a first high inductance portion 12, and a first tip portion 13 connected in series from the input terminal 16 side.
  • the sum of the electrical lengths of the first low inductance portion 11, the first high inductance portion 12, and the first tip portion 13 is 1/4 wavelength of the second frequency.
  • the signal in the second frequency band including the second frequency resonates in the antenna unit 10.
  • the position where the antenna portion 10 is connected to the input terminal 16 is not particularly limited, but in the present embodiment, the input terminal 16 is arranged at the end of the first low inductance portion 11 on the grounding portion 20 side. More specifically, the input terminal 16 is arranged only at the end portion of the first low inductance portion 11 on the grounding portion 20 side, and is not arranged at the first high inductance portion 12 and the first tip portion 13.
  • the end of the first low inductance portion 11 is, for example, a range of 10% or less of the length of the first low inductance portion 11 in the Y-axis direction from the end of the first low inductance portion 11 on the grounding portion 20 side. Means the area of.
  • the antenna portion 10 is a conductive member patterned on the main surface 41 of the substrate 40, and is formed of, for example, a metal film such as a copper film. Further, the first low inductance portion 11, the first high inductance portion 12, and the first tip portion 13 are arranged in the Y-axis direction of FIG. As a result, the Y-axis direction in FIG. 1 becomes the longitudinal direction of the antenna portion 10 and the resonance direction of the signal in the antenna portion 10. As shown in FIG. 1, the widths of the first low inductance portion 11, the first high inductance portion 12, and the first tip portion 13 (that is, the direction perpendicular to the resonance direction and parallel to the main surface 41 of the substrate 40). Dimensions) are the same.
  • the first low inductance portion 11 is a portion of the antenna portion 10 connected to the input terminal 16.
  • the input terminal 16 is connected to one end of the first low inductance portion 11, and the first high inductance portion 12 is connected to the other end.
  • the electrical length of the first low inductance portion 11 is 1/4 wavelength of the first frequency.
  • the first low inductance section 11 has a lower inductance than the first high inductance section 12.
  • the first low inductance portion 11 has a meander shape, but does not function as a choke coil for signals in the first frequency band and the second frequency band. It has a low inductance (that is, it does not block the signal).
  • the dimension of the first low inductance portion 11 in the resonance direction that is, the Y-axis direction in FIG. 1 can be reduced.
  • the first high inductance portion 12 is a portion of the antenna portion 10 that is arranged between the first low inductance portion 11 and the first tip portion 13, and has a meander shape.
  • the first high inductance section 12 has a higher inductance than the first low inductance section 11.
  • the meander shape of the first high inductance portion 12 has a smaller line width and spacing than the meander shape of the first low inductance portion 11. As a result, the inductance of the first high inductance section 12 becomes higher than that of the first low inductance section 11.
  • the first high inductance portion 12 has a line width of 0.1 mm, an interval of 0.1 mm, a length (dimension in the Y-axis direction in FIG.
  • the first high inductance unit 12 functions as a choke coil for signals in the first frequency band. That is, the effective electric length of the antenna unit 10 with respect to the signal of the first frequency band input from the input terminal 16 connected to the first low inductance unit 11 is the electric length of the first low inductance unit 11 (first frequency). 1/4 wavelength). Therefore, in the antenna unit 10, the signal in the first frequency band resonates.
  • the first high inductance unit 12 has a low inductance that does not function as a choke coil with respect to a signal in the second frequency band. Therefore, the first high inductance unit 12 does not block the signal in the second frequency band. Therefore, the signal in the second frequency band resonates in the path including the first low inductance portion 11, the first high inductance portion 12, and the first tip portion 13 of the antenna portion 10.
  • the first tip portion 13 is a portion of the antenna portion 10 arranged at the end portion farthest from the input terminal 16 in the resonance direction.
  • the shape of the first tip portion 13 is not particularly limited, but is rectangular in the present embodiment. As a result, for example, the current density at the first tip portion 13 can be increased as compared with the case where the first tip portion 13 has a meander shape, so that the radiation efficiency of radio waves from the first tip portion 13 can be increased.
  • the grounding portion 20 is a conductive member arranged on the substrate 40 and insulated from the input terminal 16.
  • the grounding portion 20 is arranged at a distance of a predetermined distance from the antenna portion 10 in the resonance direction.
  • the distance between the antenna portion 10 and the grounding portion 20 is, for example, greater than 0 and less than or equal to about 1 mm. In the present embodiment, the distance between the antenna portion 10 and the grounding portion 20 is 0.5 mm.
  • the width of the grounding portion 20 (that is, the dimension in the direction perpendicular to the resonance direction and parallel to the main surface 41 of the substrate 40) is wider than the width of the antenna portion 10.
  • the grounding portion 20 has a second low inductance portion 21, a second high inductance portion 22, and a second tip portion 23 connected in series from the input terminal 16 side.
  • the grounding portion 20 is a conductive member patterned on the main surface 41 of the substrate 40, and is formed of, for example, a metal film such as a copper film.
  • the second low inductance portion 21, the second high inductance portion 22, and the second tip portion 23 are arranged in the Y-axis direction of FIG.
  • the total electric length of the second low inductance portion 21, the second high inductance portion 22, and the second tip portion 23 is such that the directivity of the second frequency radio wave radiated from the antenna portion 10 is the longitudinal direction of the antenna portion 10 ( That is, it is set to spread along a plane perpendicular to the Y-axis direction of FIG. 1 (that is, a plane parallel to the ZX plane of FIG. 1).
  • the relationship between the total electric length and the directivity of the radio wave of the second frequency can be obtained by, for example, simulation.
  • the grounding portion 20 is connected to the grounding terminal 26.
  • the arrangement of the ground terminal 26 is not particularly limited, but in the present embodiment, the ground terminal 26 is arranged at the end of the second low inductance portion 21 on the antenna portion 10 side (that is, the input terminal 16 side). More specifically, the two ground terminals 26 are arranged only at the end of the second low inductance portion 21 on the antenna portion 10 side, and are not arranged at the second high inductance portion 22 and the second tip portion 23.
  • the end of the second low inductance portion 21 is, for example, the length of the second low inductance portion 21 in the resonance direction (Y-axis direction in FIG. 1) from the end of the second low inductance portion 21 on the antenna portion 10 side. It means an area in the range of 10% or less of the inductance.
  • the second low inductance portion 21 is a portion of the grounding portion 20 that is arranged at the position closest to the antenna portion 10.
  • the ground terminal 26 is connected to one end of the second low inductance portion 21, and the second high inductance portion 22 is connected to the other end.
  • the electrical length of the second low inductance section 21 is set so that the directivity of the first frequency radio wave radiated from the antenna section 10 spreads along a plane perpendicular to the longitudinal direction of the antenna section 10.
  • the relationship between the electric length of the second low inductance portion 21 and the directivity of the radio wave of the first frequency can be obtained by, for example, simulation.
  • the second low inductance section 21 has a lower inductance than the second high inductance section 22.
  • the second low inductance portion 21 has a rectangular shape, but the shape of the second low inductance portion 21 is not limited to this.
  • the shape of the second low inductance portion 21 is designed so that the inductance of the second low inductance portion 21 has such a low inductance that it does not function as a choke coil with respect to the signals of the first frequency and the second frequency. Good.
  • the second high inductance portion 22 is a portion of the grounding portion 20 that is arranged between the second low inductance portion 21 and the second tip portion 23, and has a meander shape.
  • the second high inductance section 22 has a higher inductance than the second low inductance section 21.
  • the second high inductance unit 22 functions as a choke coil for signals in the first frequency band. That is, the effective electrical length of the grounding portion 20 with respect to the signal in the first frequency band induced in the second low inductance portion 21 is the electrical length of the second low inductance portion 21. Further, the second high inductance unit 22 has a low inductance that does not function as a choke coil with respect to a signal in the second frequency band.
  • the second high inductance unit 22 does not block the signal in the second frequency band. Therefore, the effective electrical length of the grounding portion 20 with respect to the signal in the second frequency band includes the electrical length of the path including the second high inductance portion 22 of the grounding portion 20.
  • the second high inductance section 22 has two high inductance elements 22a and 22b connected to both ends of the second low inductance section 21 in the width direction (X-axis direction in FIG. 1), respectively.
  • An opening 22c is formed between the two high inductance elements 22a and 22b. That is, a region in which the conductive member is not arranged is formed between the two high inductance elements 22a and 22b. The region corresponding to the opening 22c of the substrate 40 may not be provided with an opening.
  • Each of the two high inductance elements 22a and 22b has a meander shape. Further, the two high inductance elements 22a and 22b have a structure that is horizontally inverted from each other.
  • the electrical lengths of the two high inductance elements 22a and 22b are equal.
  • the electric length of the second high inductance portion 22 of the multi-band antenna 1 is defined as the electric length of one of the two high inductance elements 22a and 22b.
  • the line width and pitch of the two high inductance elements 22a and 22b in the meander-shaped portion may be the same as the line width and pitch of the first high-inductance portion 12 of the antenna portion 10 in the meander-shaped portion, respectively. This makes it possible to facilitate the design of the multi-band antenna 1.
  • the current indicated by the broken line arrow in FIG. 1 is either the high inductance element 22a or the high inductance element 22b. Pass through.
  • the second tip portion 23 is a portion of the grounding portion 20 arranged at the end portion farthest from the antenna portion 10 in the resonance direction.
  • the shape of the second tip portion 23 is not particularly limited, but in the present embodiment, the second tip portion 23 has a rectangular shape.
  • the second tip portion 23 connects the two high inductance elements 22a and 22b of the second high inductance portion 22. As a result, in the second tip portion 23, the current components flowing from the two high inductance elements 22a and 22b into the second tip portion 23 can be canceled out, so that the radiation of radio waves spreading in the resonance direction due to these current components can be suppressed. ..
  • FIG. 2 is a plan view showing the configuration of the multi-band antenna 1001 according to the comparative example.
  • FIG. 2 shows a plan view of the substrate 40 of the multi-band antenna 1001 according to the comparative example in a plan view.
  • 3 and 4 are diagrams showing an outline of the directivity of the multi-band antenna according to the present embodiment and the comparative example at the first frequency, respectively.
  • the multi-band antenna 1001 according to the comparative example shown in FIG. 2 has a substrate 40, an input terminal 16, a ground terminal 26, an antenna portion 10, and a ground portion, similarly to the multi-band antenna 1 according to the present embodiment. It is equipped with 1020.
  • the multi-band antenna 1001 according to the comparative example is different from the multi-band antenna 1 according to the present embodiment in the configuration of the grounding portion 1020, and is consistent in other respects.
  • the grounding portion 1020 according to the comparative example has an electric length equivalent to the electric length of the entire grounding portion 20 according to the present embodiment.
  • the ground contact portion 1020 according to the comparative example has a flat plate shape. In other words, the grounding portion 1020 according to the comparative example has the same configuration as the second low inductance portion 21 of the grounding portion 20 according to the present embodiment as a whole.
  • the directivity of the radio wave of the second frequency radiated from the antenna portion 10 is along the plane perpendicular to the longitudinal direction of the antenna portion 10.
  • the electric length of the entire ground contact portion 20 is set so as to spread. Since the grounding portion 1020 according to the comparative example also has an electric length equivalent to that of the grounding portion 20 according to the present embodiment, the multi-band antenna 1001 according to the comparative example also has a second frequency radio wave radiated from the antenna portion 10. The directivity extends along a plane perpendicular to the longitudinal direction of the antenna portion 10.
  • the multi-band antenna 1 includes the second high inductance section 22 which functions as a choke coil with respect to the signal of the first frequency, so that the second low inductance section 21
  • the effective electrical length of the grounding section 20 is equal to the electrical length of the second low inductance section 21.
  • the electrical length of the second low inductance section 21 is set so that the directivity of the first frequency radio wave radiated from the antenna section 10 spreads along a plane perpendicular to the longitudinal direction of the antenna section 10. .. Therefore, as shown in FIG. 3, the directivity of the radio wave of the first frequency spreads along the plane perpendicular to the longitudinal direction of the antenna portion 10.
  • the electric length for the signal of the first frequency is the same as the electric length for the second frequency, and the entire grounding portion 1020. Is equal to the electrical length of.
  • the directivity of the radio wave of the first frequency is closer to the grounding portion 20 with respect to the plane perpendicular to the longitudinal direction of the antenna portion 10. It spreads diagonally (that is, diagonally downward in FIG. 4). Although only the directivity in the plane parallel to the XY plane is shown in FIG.
  • the multi-band antenna 1001 passes through the input terminal 16 of the multi-band antenna 1001 and is parallel to the Y axis in all the planes.
  • the directivity of is the same as that of FIG. This is because, in the multi-band antenna 1001 according to the comparative example, the effective electric length of the grounding portion 1020 with respect to the signal of the first frequency is longer than that of the multi-band antenna 1 according to the present embodiment, so that the grounding portion 1020 It is considered that this is because the electric field component generated by the current flowing into the tip portion becomes stronger than the electric field component generated by the antenna portion 10.
  • the grounding portion 20 has the second high inductance portion 22 having a meander shape, so that the effective electricity of the grounding portion 20 with respect to the first frequency is obtained.
  • the length can be shorter than the effective electrical length for the second frequency signal. Therefore, by appropriately setting the effective electric length of the grounding portion 20 for each signal of the first frequency and the second frequency, it is possible to realize the directivity perpendicular to the resonance direction in the frequency band including each frequency. ..
  • Such a multi-band antenna 1 is particularly effective when used in an array antenna, for example. That is, since the multi-band antenna 1 has a directivity perpendicular to the resonance direction, each multi-band antenna radiates when a plurality of multi-band antennas 1 are arranged in a direction perpendicular to the resonance direction to form an array antenna. It is possible to enhance the interaction between the radio waves.
  • 5 and 6 are graphs showing an example of a simulation result of directivity of the multi-band antenna 1 according to the present embodiment.
  • 5 and 6 show simulation results when the inductance of each high inductance element of the second high inductance portion 22 is 6 nH and 7 nH, respectively.
  • the width Wg of the ground contact portion 20 (that is, the dimension in the direction perpendicular to the resonance direction and parallel to the main surface 41 of the substrate 40) is set to 7 mm.
  • the directivity in each case where the frequency of the signal of the first frequency band input to the input terminal 16 is 5.0 GHz, 5.2 GHz, 5.4 GHz, 5.6 GHz, 5.8 GHz, and 6.0 GHz.
  • the sex is shown.
  • the angle ⁇ yx in each figure indicates an angle of inclination from the Y-axis direction to the X-axis direction in each figure.
  • FIG. 7 is a graph showing the relationship between the width Wg of the grounding portion 20 and the minimum inductance value Lmin of each high inductance element of the second high inductance portion 22 according to the present embodiment.
  • the minimum inductance value Lmin means the inductance value of each high inductance element required to realize directivity substantially perpendicular to the resonance direction with respect to the signal in the first frequency band. In the graph shown in FIG. 7, the minimum inductance value Lmin when the first frequency band is the 5 GHz band is shown.
  • the minimum inductance values Lmin of each high inductance element are 5 nH, 4 nH and 2.5 nH, respectively. From this, it can be seen that when the width Wg of the grounding portion 20 is 7 mm or more, the minimum inductance value Lmin of each high inductance element is 7 nH or more.
  • the antenna module according to the second embodiment will be described.
  • the antenna module according to the present embodiment is an application example of the multi-band antenna 1 according to the first embodiment.
  • 8 and 9 are first and second plan views showing the configuration of the antenna module 100 according to the present embodiment, respectively.
  • FIG. 8 a plan view of one main surface 141 of the substrate 140 of the antenna module 100 in a plan view is shown.
  • FIG. 9 a plan view of each component arranged on the main surface on the back side of the main surface 141 on the substrate 140 is shown, and the outline of the substrate 140 is also shown by a dotted line.
  • the antenna module 100 is a module including an array antenna 101 and a distributor that distributes signals to each multi-band antenna constituting the array antenna 101.
  • the antenna module 100 is a module that performs wireless communication based on the wireless LAN standard, and transmits / receives signals in the 5 GHz band and the 2.4 GHz band as the first frequency band and the second frequency band, respectively.
  • the antenna module 100 includes a 3 distributor 106 as a distributor.
  • the antenna module 100 includes a ground electrode 190, lines 61, 62, 63, 71, 72 and 73, a phase shifter 80, and ground wiring 71 g, 72 g and 73 g. It further includes a connector Cn and a control terminal Ts.
  • the array antenna 101 is an antenna having a plurality of multi-band antennas.
  • the array antenna 101 has three multi-band antennas 1a, 1b and 1c.
  • the three multi-band antennas 1a, 1b and 1c share a substrate 140.
  • other components of the antenna module 100 are also arranged on the substrate 140.
  • the configurations of the three multi-band antennas 1a, 1b, and 1c other than the substrate 140 are the same as those of the multi-band antenna 1 according to the first embodiment.
  • the three multi-band antennas 1a, 1b and 1c are arranged in a direction (that is, an X-axis direction) perpendicular to their respective resonance directions (that is, the Y-axis direction).
  • the multi-band antennas 1a, 1b and 1c have directivity perpendicular to the resonance direction as described in the first embodiment, the multi-band antennas 1a, 1b and 1c are arranged in a direction perpendicular to the resonance direction and arranged in an array.
  • the antenna is configured, the interaction between the radio waves radiated by each multi-band antenna can be enhanced.
  • the substrate 140 has the same configuration as the substrate 40 according to the first embodiment.
  • the antenna portion 10 and the ground portion 20 of each multi-band antenna are arranged on one main surface 141 of the substrate 140.
  • the ground electrode 190 is an electrode connected to the ground.
  • the ground electrode 190 is arranged on the main surface 141 of the substrate 140. In the present embodiment, the ground electrode 190 is arranged at a position adjacent to the ground portion 20 of each multi-band antenna of the array antenna 101.
  • the ground electrode 190 also functions as a shield wiring for each line arranged on the main surface on the back side of the main surface 141 of the substrate 140.
  • the ground electrode 190 is, for example, a conductive member patterned on the main surface 141 of the substrate 140, and is formed of, for example, a metal film such as a copper film.
  • the ground electrode 190 is connected to each of the conductive members arranged on the main surface on the back side of the main surface 141 of the substrate 140 via the via wiring penetrating the substrate 140 at the terminals 196a to 196c, 197, 198 and 199. ..
  • the 3-distributor 106 is a distributor that distributes signals in the first frequency band and the second frequency band into three.
  • the three distributor 106 according to the present embodiment will be described with reference to FIG.
  • FIG. 10 is a plan view showing the configuration of the three distributor 106 according to the present embodiment. In FIG. 10, the inside of the broken line frame shown in FIG. 9 is enlarged and shown.
  • the 3 distributor 106 includes an input terminal T0, a first output terminal T1, a second output terminal T2, a third output terminal T3, a first transmission line L1, and a second transmission. It includes a line L2, a third transmission line L3, a first resistor R1, a second resistor R2, a third resistor R3, and a fourth resistor R4.
  • Input terminal T0 is a terminal to which a signal is input.
  • signals in the first frequency band including the first frequency and the second frequency band including the second frequency lower than the first frequency are input to the input terminal T0.
  • the first output terminal T1, the second output terminal T2, and the third output terminal T3 are terminals that output three distributed signals in which the signal input from the input terminal T0 is divided into three, respectively.
  • the three distributed signals having the same phase are output from the first output terminal T1, the second output terminal T2, and the third output terminal T3, respectively.
  • the first transmission line L1, the second transmission line L2, and the third transmission line L3 are lines connecting the input terminal T0 and the first output terminal T1, the second output terminal T2, and the third output terminal T3, respectively. ..
  • the first transmission line L1 includes a first input side line L11 and a first output side line L12 connected in series at the first connection point CP1 in order from the input terminal T0 side.
  • the second transmission line L2 includes a second input side line L21 and a second output side line L22 connected in series at the second connection point CP2 in order from the input terminal T0 side.
  • the third transmission line L3 includes a third input side line L31 and a third output side line L32 connected in series at the third connection point CP3 in order from the input terminal T0 side.
  • the width of the second input side line L21 is narrower than the width of the first input side line L11 and the third input side line L31. In this way, by narrowing the width of the second input side line L21, the second input side line L21 is curved to secure the electric length, and the first input side line L11 and the third input side line L31 It becomes easy to fit the second input side line L21 in the sandwiched area.
  • the width of the second output side line L22 is narrower than the width of the first output side line L12 and the third output side line L32. In this way, by narrowing the width of the second output side line L22, the second output side line L22 is curved to secure the electric length, and the first output side line L12 and the third output side line L32 It becomes easy to fit the second output side line L22 in the sandwiched region.
  • the electrical length of each of the first input side line L11, the second input side line L21, and the third input side line L31 is 1/4 wavelength of the first frequency.
  • the electrical length of each of the first transmission line L1, the second transmission line L2, and the third transmission line L3 is 1/4 wavelength of the second frequency lower than the first frequency.
  • the terminal T3 and the second output terminal T2 are connected via a first resistor R1, a second resistor R2, a third resistor R3, and a fourth resistor R4, respectively.
  • the first resistor R1, the second resistor R2, the third resistor R3, and the fourth resistor R4 are absorption resistors.
  • the resistance values of the 3rd resistor R3 and the 4th resistor R4 are 100 ⁇ , which is twice the impedance on the output side, and the 1st resistor R1 and the 2nd resistor are
  • the resistance value of the resistor R2 is twice or more and four times or less the impedance on the output side, that is, 100 ⁇ or more and 200 ⁇ or less.
  • the resistance values of the first resistor R1, the second resistor R2, the third resistor R3, and the fourth resistor R4 are the same, and all of them are 100 ⁇ .
  • the three distributor 106 according to the present embodiment has the effect of being smaller than a general Wilkinson type distributor by having the above configuration.
  • the electrical lengths of the lines corresponding to the first output side line L12, the second output side line L22, and the third output side line L32 of the three distributor 106 according to the present embodiment are set to the second. It needs to be 1/4 wavelength of 2 frequencies.
  • an absorption resistor is provided between the first connection point CP1 and the second connection point CP2 and between the third connection point CP3 and the second connection point CP2.
  • the electrical length of the first transmission line L1, the second transmission line L2, and the third transmission line L3 can be set to 1/4 wavelength of the second frequency. Therefore, in the three-distributor 106 according to the present embodiment, the electrical lengths of the first transmission line L1, the second transmission line L2, and the third transmission line L3 are distributed by the Wilkinson type by only 1/4 wavelength of the first frequency. It can be made smaller than a vessel. As a result, the antenna module 100 can be miniaturized.
  • the connector Cn is a connecting member for inputting a signal to the antenna module 100 from the outside.
  • the configuration of the connector Cn is not particularly limited, but in the present embodiment, it is a coaxial connector.
  • the signal wiring of the connector Cn is connected to the input terminal T0 of the 3 distributor 106. As a result, a signal can be input to the 3 distributor 106 from the outside via the connector Cn.
  • the connector Cn has a connector ground Cg connected to the ground.
  • the shield wiring of the connector Cn is connected to the connector ground Cg.
  • the connector ground Cg is connected to the terminal 198 of the ground electrode 190 via the via wiring penetrating the substrate 140.
  • the line 61 is a conductive member that connects the line 71 and the first output terminal T1 of the 3 distributor 106.
  • the electric length of the line 61 is set based on the phase difference given between the distributed signals distributed to the lines 71 to 73 and the electric lengths of the lines 62 and 63.
  • a phase shifter 80 is connected to the line 61, and the amount of phase delay in the line 61 changes according to the state of the phase shifter 80.
  • the line 62 is a conductive member that connects the line 72 and the second output terminal T2 of the 3 distributor 106.
  • the electric length of the line 62 is set based on the phase difference given between the distributed signals distributed to the lines 71 to 73 and the electric length of the lines 61 and 63.
  • the line 63 is a conductive member that connects the line 73 and the third output terminal T3 of the 3 distributor 106.
  • the electric length of the line 63 is set based on the phase difference given between the distributed signals distributed to the lines 71 to 73 and the electric lengths of the lines 61 and 62.
  • the phase shifter 80 is a device connected to the line 61 and changing the amount of phase delay of the distributed signal on the line 61.
  • the phase shifter 80 is a loaded line type phase shifter.
  • the phase shifter 80 has lines 81 and 82, capacitors 83 and 84, PIN diodes 86 and 87, and a ground electrode 85.
  • the line 81 is a line coupled to the line 61 via a capacitor 83. One end of the line 81 is connected to the capacitor 83 and the other end is connected to the PIN diode 86.
  • the line 82 is a line coupled to the line 61 via a capacitor 84.
  • the line 82 is coupled to the line 61 at a position different from the position where the line 81 is connected.
  • One end of the line 82 is connected to the capacitor 84 and the other end is connected to the PIN diode 87.
  • the capacitors 83 and 84 are elements for connecting the line 61 and the lines 81 and 82, respectively.
  • the phase shifter 80 and the line 61 are coupled by capacitors 83 and 84.
  • the ground electrode 85 is an electrode connected to the ground.
  • the ground electrode 190 is connected to the terminal 197 via a via wiring penetrating the substrate 140.
  • the PIN diodes 86 and 87 are switches that switch the connection state between the lines 81 and 82 and the ground electrode 85, respectively, between the open state and the closed state.
  • the PIN diodes 86 and 87 are controlled by a control signal input to the control terminals Ts.
  • the phase delay amount of the distributed signal on the line 61 can be switched by setting the states of the PIN diodes 86 and 87 in the open state or the closed state together.
  • the control terminal Ts is a terminal to which a control signal for controlling the states of the PIN diodes 86 and 87 of the phase shifter 80 is input.
  • the control terminal Ts has a ground terminal, and the ground terminal is connected to the terminal 191 on the substrate 140 and the terminal 199 of the ground electrode 190 via the via wiring penetrating the substrate 140.
  • Each of the lines 71, 72, and 73 is a long conductive member to which the distribution signal distributed by the three distributor 106 is input, and is in the Y-axis direction of FIG. 9 (that is, the resonance direction of each multi-band antenna). ).
  • one end of the line 71 is connected to the line 61.
  • a terminal 74 is arranged at the other end of the line 71.
  • the terminal 74 is connected to the input terminal 16 of the multi-band antenna 1a via a via wiring penetrating the substrate 140.
  • the line 71 receives the distribution signal from the first output terminal T1 of the 3 distributor 106 via the line 61, and outputs the distribution signal to the multi-band antenna 1a.
  • One end of the line 72 is connected to the line 62.
  • a terminal 76 is arranged at the other end of the line 72.
  • the terminal 76 is connected to the input terminal 16 of the multi-band antenna 1b via a via wiring penetrating the substrate 140.
  • the line 72 receives the distribution signal from the second output terminal T2 of the 3 distributor 106 via the line 62, and outputs the distribution signal to the multi-band antenna 1b.
  • One end of the line 73 is connected to the line 63.
  • a terminal 78 is arranged at the other end of the line 73.
  • the terminal 78 is connected to the input terminal 16 of the multi-band antenna 1c via a via wiring penetrating the substrate 140.
  • the line 73 receives the distribution signal from the third output terminal T3 of the 3 distributor 106 via the line 63, and outputs the distribution signal to the multi-band antenna 1c.
  • Each of the two ground wires 71g is a long conductive member connected to the ground and arranged along the line 71, and extends in the Y-axis direction of FIG.
  • the two ground wires 71 g are arranged in the X-axis direction of FIG. 9, and the line 71 is arranged between the two ground wires 71 g.
  • the two ground wires 71g and the line 71 are arranged apart from each other.
  • a terminal 75g is arranged at one end of each of the two ground wires 71g, and a terminal 74g is arranged at the other end.
  • the terminal 75g is connected to the terminal 196a of the ground electrode 190 via a via wiring penetrating the substrate 140.
  • the terminal 74g is connected to the ground terminal 26 of the ground portion 20 of the multi-band antenna 1a via a via wiring penetrating the substrate 140.
  • Each of the two grounding wires 72g is a long conductive member connected to the ground and arranged along the line 72, and extends in the Y-axis direction of FIG.
  • the two ground wires 72 g are arranged in the X-axis direction of FIG. 9, and the line 72 is arranged between the two ground wires 72 g.
  • the two ground wires 72 g and the line 72 are arranged apart from each other.
  • a terminal 77g is arranged at one end of each of the two ground wires 72g, and a terminal 76g is arranged at the other end.
  • the terminal 77g is connected to the terminal 196b of the ground electrode 190 via the via wiring penetrating the substrate 140.
  • the terminal 76g is connected to the ground terminal 26 of the ground portion 20 of the multi-band antenna 1b via a via wiring penetrating the substrate 140.
  • Each of the two ground wires 73g is a long conductive member connected to the ground and arranged along the line 73, and extends in the Y-axis direction of FIG.
  • the two ground wires 73g are arranged in the X-axis direction of FIG. 9, and the line 73 is arranged between the two ground wires 73g.
  • the two ground wires 73g and the line 73 are arranged apart from each other.
  • a terminal 79g is arranged at one end of each of the two ground wires 73g, and a terminal 78g is arranged at the other end.
  • the terminal 79g is connected to the terminal 196c of the ground electrode 190 via the via wiring penetrating the substrate 140.
  • the terminal 78g is connected to the ground terminal 26 of the ground portion 20 of the multi-band antenna 1c via a via wiring penetrating the substrate 140.
  • the transmission lines, lines 61, 62, 63, 71 to 73, 81 and 82 of the three distributor 106 according to the present embodiment, and the ground wirings 71g, 72g and 73g are, for example, the main surface 141 of the substrate 140. It is a conductive member patterned on the main surface on the back side, and is formed of, for example, a metal film such as a copper film.
  • the lines 71, 72 and 73 form a coplanar line together with the ground wires 71 g, 72 g and 73 g, respectively.
  • the transmission lines of the three distributor 106 and the lines 61, 62 and 63 of the phase shifter 80 and the lines 81 and 82 of the phase shifter 80 according to the present embodiment are arranged at positions facing the ground electrode 190 via the substrate 140. Has been done. As a result, each line and the ground electrode 190 form a microstrip line.
  • the line 71 and the ground wiring 71g shown in FIG. 9 are arranged at positions facing the ground portion 20 of the multi-band antenna 1a shown in FIG.
  • the width (dimension in the X-axis direction) of the grounding portion 20 is the portion of the two grounding wires 71g that is arranged along the line 71 (that is, in the example shown in FIG. 9, the terminal 75g of the grounding wiring 71g. It is larger than the distance between the outer edges in the X-axis direction (the portion excluding the periphery of). That is, the grounding portion 20 projects outward from the two grounding wires 71g in the X-axis direction.
  • the width of the grounding portion 20 is 7 mm, and the distance between the outer edges of the two grounding wires 71g arranged along the line 71 in the X-axis direction is 3 mm. ..
  • the distance between the outer edges of the two grounding wires 71g arranged along the line 71 in the X-axis direction is 3 mm. ..
  • the width of the grounding portion 20 of the multi-band antennas 1b and 1c is also the same as the width of the grounding portion 20 of the multi-band antenna 1a, which is the X of the portion of the two opposing grounding wires arranged along the lines 72 and 73. Greater than the distance between the outer edges in the axial direction.
  • the operation and effect of the antenna module 100 according to the present embodiment will be described.
  • the antenna module 100 according to the present embodiment by appropriately setting the electric lengths of the lines 61, 62, and 63, the signal input to each multi-band antenna constituting the array antenna 101 can be obtained.
  • the phase can be adjusted.
  • the directivity of the array antenna 101 can be adjusted. For example, when there is an antenna near the antenna module 100 that transmits / receives signals in a frequency band close to the frequency band handled by the antenna module 100, the array antenna in the direction from the array antenna 101 of the antenna module 100 toward the other antenna.
  • the directivity of 101 it is possible to reduce the interference of radio waves between the antenna module 100 and the other antenna.
  • FIG. 11 is a graph showing the directivity of the array antenna 101 according to the present embodiment. Note that FIG. 11 shows the directivity when both the PIN diodes 86 and 87 of the phase shifter 80 of the antenna module 100 are turned off.
  • the angle ⁇ zx in FIG. 11 indicates an angle that is inclined from the Z-axis direction to the X-axis direction in each figure.
  • the directivity in the positive direction in the X-axis direction is reduced. Therefore, when there is another antenna on the positive side of the array antenna 101 having such directivity in the X-axis direction, the interference between the array antenna 101 and the other antenna can be reduced.
  • the phase shifter 80 can switch the phase of the signal input to the multi-band antenna 1a.
  • the phase of the signal input to the multi-band antenna 1a is about 50 depending on whether the PIN diodes 86 and b87 are both OFF and both are ON. ° Can be changed.
  • the effect of the phase shifter 80 will be described with reference to FIG.
  • FIG. 12 is a graph showing the directivity when the state of the phase shifter 80 of the array antenna 101 according to the present embodiment is changed.
  • FIG. 12 shows the directivity when both the PIN diodes 86 and 87 of the phase shifter 80 are turned on.
  • the angle ⁇ zx in FIG. 12 indicates an angle inclined from the Z-axis direction to the X-axis direction in each figure.
  • the directivity of the array antenna 101 can be significantly changed by the phase shifter 80.
  • the effect of the phase shifter 80 is effective when the radio wave environment around the antenna module 100 changes. For example, when the arrangement of the antenna module 100 and other antennas is changed, the relative positions of the antenna module 100 and the other antennas may change.
  • the relative positions of the antenna module 100 and the other antennas do not change, when the antenna module 100 and the other antennas are moved, the relative positions of the surrounding structures and the antenna module 100 may change.
  • the interference of the reflected radio waves may become a problem in the array antenna 101 of the antenna module 100.
  • the radio wave environment changes in this way, interference with other radio waves can be suppressed by changing the directivity of the array antenna 101 using the phase shifter 80.
  • FIG. 13 is a perspective view showing the configuration of an audio device 103 including the antenna module 100 according to the present embodiment.
  • the audio device 103 shown in FIG. 13 mainly includes a housing 103c, antenna modules 100, 100a and 104, and speakers Sp0 to Sp4.
  • a housing 103c In FIG. 13, only the outline of the housing 103c is shown by a dotted line in order to show the arrangement of each component.
  • the antenna module 100a is a module that performs wireless communication based on the wireless LAN standard like the antenna module 100, and transmits / receives signals in the 5 GHz band and the 2.4 GHz band.
  • the antenna module 100a is a module similar to the antenna module 100, and the structure and arrangement of each component are reversed left and right with respect to the antenna module 100.
  • the directivity of the array antenna included in the antenna module 100a is the one in which the directivity of the array antenna 101 of the antenna module 100 is inverted left and right (that is, the graphs shown in FIGS. 11 and 12 are inverted left and right). ).
  • the antenna module 104 is a module that performs wireless communication with other devices. In the present embodiment, it is a module that transmits a 2.4 GHz band signal to another audio device based on a standard different from the wireless LAN standard.
  • other audio equipment is, for example, a subwoofer.
  • the sound device 103 since the sound device 103 includes three antenna modules 100, 100a and 104 that handle signals in the 2.4 GHz band, radio wave interference may occur between these modules.
  • the array antenna 101 of the antenna module 100 according to the present embodiment has low directivity on the positive side in the X-axis direction as shown in FIG. 11, it is possible to reduce radio wave interference with other modules.
  • the antenna module 100a has a structure in which the antenna module 100 is flipped horizontally, the array antenna of the antenna module 100a has low directivity on the negative side in the X-axis direction. Therefore, it is possible to reduce the interference of radio waves with other antenna modules arranged on the negative side in the X-axis direction of the antenna module 100a.
  • the radio wave radiated from the antenna module 104 may be reflected by the structure and reach the antenna modules 100 and 100a.
  • the directivity of each array antenna is changed by changing the setting of each phase shifter of the antenna modules 100 and 100a. By changing, the interference with the reflected radio wave can be reduced.
  • the multi-band antenna according to the third embodiment will be described.
  • the multi-band antenna according to the present embodiment is different from the multi-band antenna 1 according to the first embodiment in the resonating frequency band.
  • the multi-band antenna according to the present embodiment will be described focusing on the differences from the multi-band antenna 1 according to the first embodiment.
  • FIG. 14 is a plan view showing the configuration of the multi-band antenna 201 according to the present embodiment.
  • FIG. 14 shows a plan view of the substrate 240 of the multi-band antenna 201 in a plan view.
  • the direction perpendicular to the main surface 241 of the substrate 240 of the multi-band antenna 201 is the Z-axis direction
  • the two directions perpendicular to the Z-axis direction and perpendicular to each other are X.
  • the multi-band antenna 201 transmits and receives a signal in the first frequency band including the first frequency and a signal in the second frequency band including the second frequency lower than the first frequency.
  • the 2.4 GHz band and the 920 MHz band are used as the first frequency band and the second frequency band, respectively.
  • the multi-band antenna 201 includes a substrate 240, an input terminal 216, an antenna portion 210, and a ground portion 220.
  • the multi-band antenna 201 further includes a ground terminal 226.
  • the board 240 is a member that serves as a base for the multi-band antenna 201.
  • the board 240 is a circuit board, and an antenna portion 210 and a grounding portion 220 are arranged on one main surface 241 of the board 240.
  • the input terminal 216 is a terminal arranged on the board 240 to input a signal.
  • the high frequency signal transmitted by the multi-band antenna 201 is input to the input terminal 216.
  • the input terminal 216 also functions as an output terminal that outputs a high-frequency signal received by the multi-band antenna 201. Further, the input terminal 216 is connected to the antenna unit 210.
  • the ground terminal 226 is a terminal arranged on the board 240 and connected to the ground.
  • the ground terminal 226 is arranged on the main surface 241 of the substrate 240 and is connected to the ground portion 220.
  • the number of ground terminals 226 is not particularly limited, but is two in the present embodiment.
  • the antenna portion 210 is a conductive member arranged on the substrate 240 and connected to the input terminal 216.
  • the signal in the first frequency band and the signal in the second frequency band resonate in the antenna unit 210.
  • radio waves are radiated from the antenna unit 210.
  • the antenna portion 210 has a first low inductance portion 211, a first high inductance portion 212, and a first tip portion 213 connected in series from the input terminal 216 side.
  • the sum of the electrical lengths of the first low inductance portion 211, the first high inductance portion 212, and the first tip portion 213 is 1/4 wavelength of the second frequency.
  • the signal in the second frequency band including the second frequency resonates in the antenna unit 210.
  • the position where the antenna portion 210 is connected to the input terminal 216 is not particularly limited, but in the present embodiment, the input terminal 216 is arranged at the end of the first low inductance portion 211 on the grounding portion 220 side. More specifically, the input terminal 216 is arranged only at the end of the first low inductance portion 211 on the grounding portion 220 side, and is not arranged at the first high inductance portion 212 and the first tip portion 213.
  • the end of the first low inductance portion 211 is, for example, a range of 10% or less of the length of the first low inductance portion 211 in the Y-axis direction from the end of the first low inductance portion 211 on the grounding portion 20 side. Means the area of.
  • the first low inductance portion 211, the first high inductance portion 212, and the first tip portion 213 are arranged in the Y-axis direction of FIG.
  • the Y-axis direction in FIG. 14 becomes the longitudinal direction of the antenna portion 210 and the resonance direction of the signal in the antenna portion 210.
  • the widths of the first low inductance portion 211, the first high inductance portion 212, and the first tip portion 213 are the same.
  • the first low inductance portion 211 is a portion of the antenna portion 210 connected to the input terminal 216.
  • the input terminal 216 is connected to one end of the first low inductance portion 211, and the first high inductance portion 212 is connected to the other end.
  • the electrical length of the first low inductance portion 211 is 1/4 wavelength of the first frequency.
  • the first low inductance section 211 has a lower inductance than the first high inductance section 212.
  • the first low inductance portion 211 has a line width of 2.0 mm, an interval of 2.0 mm, and a length (Y-axis direction in FIG. 14). Dimension) 22 mm, width (dimension in the X-axis direction in FIG.
  • the first low inductance portion 211 has a meander shape, but has a low inductance such that it does not function as a choke coil (that is, does not block the signal) with respect to the signals in the first frequency band and the second frequency band. ..
  • the first low inductance portion 211 has portions that are not meander-shaped at both ends of the meander-shaped portion (that is, both ends in the Y-axis direction).
  • the total length of the two portions at both ends that are not in the shape of a meander is 7 mm. Therefore, the total length of the first low inductance portion 211 in the Y-axis direction is 29 mm.
  • the first high inductance portion 212 is a portion of the antenna portion 210 that is arranged between the first low inductance portion 211 and the first tip portion 213, and has a meander shape.
  • the first high inductance section 212 has a higher inductance than the first low inductance section 211.
  • the meander shape of the first high inductance portion 212 has a smaller line width and spacing than the meander shape of the first low inductance portion 211. As a result, the inductance of the first high inductance section 212 becomes higher than that of the first low inductance section 211.
  • the first high inductance portion 212 has a line width of 0.1 mm, an interval of 0.1 mm, a length (dimensions in the Y-axis direction in FIG. 14) of 7.1 mm, and a width (in the X-axis direction in FIG. 14). Dimensions) It has a meander shape of 7.5 mm.
  • the first high inductance portion 212 functions as a choke coil for signals in the first frequency band. That is, the effective electric length of the antenna unit 210 with respect to the signal of the first frequency band input from the input terminal 216 connected to the first low inductance unit 211 is the electric length of the first low inductance unit 211 (first frequency). 1/4 wavelength).
  • the signal in the first frequency band resonates.
  • the first high inductance portion 212 has a low inductance that does not function as a choke coil with respect to a signal in the second frequency band. Therefore, the first high inductance portion 212 does not block the signal in the second frequency band. Therefore, the signal in the second frequency band resonates in the path including the first low inductance portion 211, the first high inductance portion 212, and the first tip portion 213 of the antenna portion 210.
  • the first tip portion 213 is a portion of the antenna portion 210 arranged at the end farthest from the input terminal 216 in the resonance direction.
  • the shape of the first tip portion 213 is not particularly limited, but is rectangular in the present embodiment.
  • the grounding portion 220 is a conductive member arranged on the substrate 240 and insulated from the input terminal 216.
  • the grounding portion 220 is arranged at a distance from the antenna portion 210 by a predetermined distance in the resonance direction.
  • the distance between the antenna portion 210 and the grounding portion 220 is, for example, greater than 0 and less than or equal to about 3 mm. In the present embodiment, the distance between the antenna portion 210 and the grounding portion 220 is 2.0 mm.
  • the width of the grounding portion 220 (that is, the dimension in the direction perpendicular to the resonance direction and parallel to the main surface 241 of the substrate 240) is wider than the width of the antenna portion 210.
  • the grounding portion 220 has a second low inductance portion 221, a second high inductance portion 222, and a second tip portion 223 connected in series from the input terminal 216 side. Further, the second low inductance portion 221 and the second high inductance portion 222 and the second tip portion 223 are arranged in the Y-axis direction of FIG.
  • the total electrical lengths of the second low inductance section 221 and the second high inductance section 222 and the second tip section 223 are such that the directivity of the second frequency radio wave radiated from the antenna section 210 is the longitudinal direction of the antenna section 210. That is, it is set to spread along a plane perpendicular to the Y-axis direction of FIG. 14 (that is, a plane parallel to the ZX plane of FIG. 14).
  • the grounding portion 220 is connected to the grounding terminal 226.
  • the arrangement of the ground terminal 226 is not particularly limited, but in the present embodiment, the ground terminal 226 is arranged at the end of the second low inductance portion 221 on the antenna portion 210 side (that is, the input terminal 216 side). More specifically, the two ground terminals 226 are arranged only at the end of the second low inductance portion 221 on the antenna portion 210 side, and are not arranged at the second high inductance portion 222 and the second tip portion 223.
  • the end of the second low inductance portion 221 is, for example, the length of the second low inductance portion 221 in the resonance direction (Y-axis direction in FIG. 14) from the end of the second low inductance portion 221 on the antenna portion 210 side. It means an area in the range of 10% or less of the inductance.
  • the second low inductance portion 221 is a portion of the grounding portion 220 that is arranged at the position closest to the antenna portion 210.
  • the ground terminal 226 is connected to one end of the second low inductance portion 221 and the second high inductance portion 222 is connected to the other end.
  • the electrical length of the second low inductance section 221 is set so that the directivity of the first frequency radio wave radiated from the antenna section 10 spreads along a plane perpendicular to the longitudinal direction of the antenna section 210.
  • the second low inductance section 221 has a lower inductance than the second high inductance section 222.
  • the second low inductance portion 221 has a rectangular shape, but the shape of the second low inductance portion 221 is not limited to this.
  • the shape of the second low inductance portion 221 is designed so that the inductance of the second low inductance portion 221 has such a low inductance that it does not function as a choke coil with respect to the signals of the first frequency and the second frequency. Good.
  • the second high inductance portion 222 is a portion of the grounding portion 220 that is arranged between the second low inductance portion 221 and the second tip portion 223, and has a meander shape.
  • the second high inductance section 222 has a higher inductance than the second low inductance section 221.
  • the second high inductance section 222 functions as a choke coil for signals in the first frequency band. That is, the effective electrical length of the grounding portion 220 with respect to the signal in the first frequency band induced in the second low inductance portion 221 is the electrical length of the second low inductance portion 221. Further, the second high inductance portion 222 has a low inductance that does not function as a choke coil with respect to a signal in the second frequency band.
  • the second high inductance section 222 does not block the signal in the second frequency band. Therefore, the effective electrical length of the grounding portion 220 with respect to the signal in the second frequency band includes the electrical length of the path including the second high inductance portion 222 of the grounding portion 220.
  • the second high inductance portion 222 has two high inductance elements 222a and 222b connected to both ends of the second low inductance portion 221 in the width direction (X-axis direction in FIG. 14), respectively.
  • An opening 222c is formed between the two high inductance elements 222a and 222b. That is, a region in which the conductive member is not arranged is formed between the two high inductance elements 222a and 222b. An opening may not be provided in the region corresponding to the opening 222c of the substrate 240.
  • Each of the two high inductance elements 222a and 222b has a meander shape. Further, the two high inductance elements 222a and 222b have a structure that is horizontally inverted from each other.
  • the electrical lengths of the two high inductance elements 222a and 222b are equal.
  • the electric length of the second high inductance portion 222 of the multi-band antenna 201 is defined as the electric length of one of the two high inductance elements 222a and 222b.
  • the line width and pitch of the two high inductance elements 222a and 222b in the meander-shaped portion may be the same as the line width and pitch of the first high-inductance portion 212 of the antenna portion 210 in the meander-shaped portion, respectively.
  • a current corresponding to radio waves transmitted and received flows mainly along the edge edge. Therefore, by arranging the two high inductance elements 222a and 222b at the widthwise ends of the grounding portion 220, the current passes through either the high inductance element 222a and the high inductance element 222b.
  • the second tip portion 223 is a portion of the grounding portion 220 arranged at the end portion farthest from the antenna portion 210 in the resonance direction.
  • the second tip portion 223 has a rectangular shape. Further, the second tip portion 223 connects the two high inductance elements 222a and 222b of the second high inductance portion 222.
  • 15 and 16 are graphs showing an example of a simulation result of directivity of the multi-band antenna 201 according to the present embodiment.
  • 15 and 16 show simulation results when the inductance of each high inductance element of the second high inductance portion 222 is 37.5 nH and 45 nH, respectively.
  • the width Wg of the ground contact portion 220 (that is, the dimension in the direction perpendicular to the resonance direction and parallel to the main surface 41 of the substrate 40) is set to 20 mm.
  • the directivity in each case where the frequencies of the signals of the first frequency band and the second frequency band input to the input terminal 216 are 2.45 GHz and 920 MHz, respectively, is shown.
  • each high inductance element when the inductance of each high inductance element is less than 45 nH, directivity perpendicular to the resonance direction cannot be realized. It is considered that this is because the function of each high inductance element as a choke coil did not work sufficiently for a signal having a frequency of 2.45 GHz.
  • FIG. 17 is a graph showing the relationship between the width Wg of the grounding portion 220 and the minimum inductance value Lmin of each high inductance element of the second high inductance portion 222 according to the present embodiment.
  • the minimum inductance value Lmin means the inductance value of each high inductance element required to realize directivity substantially perpendicular to the resonance direction with respect to the signal in the first frequency band. In the graph shown in FIG. 17, the minimum inductance value Lmin when the first frequency band is the 2.45 GHz band is shown.
  • the minimum inductance value Lmin of each high inductance element is 55 nH, respectively. It was 50 nH, 45 nH, 45 nH, 45 nH and 35 nH. From this, it can be seen that when the width Wg of the grounding portion 220 is 15 mm or more, the minimum inductance value Lmin of each high inductance element is 55 nH or more.
  • the multi-band antenna 1 a dual band example of transmitting and receiving signals of two frequency bands has been shown, but the multi-band antenna of the present disclosure may transmit and receive three or more frequency bands.
  • a multi-band antenna that transmits and receives a third frequency band including a third frequency lower than the first frequency and higher than the second frequency in addition to the first frequency band and the second frequency band can be realized.
  • the first middle inductance section is inserted between the first low inductance section 11 and the first high inductance section 12, and the second low inductance section 21 and the second By inserting the second middle inductance section between the high inductance section 22 and the high inductance section 22, it is possible to realize a multi-band antenna capable of transmitting and receiving signals in three frequency bands from the first frequency band to the third frequency band.
  • the first middle inductance portion has a higher inductance than the first low inductance portion 11 and a lower inductance than the first high inductance portion 12.
  • the second middle inductance section has a higher inductance than the second low inductance section 21 and a lower inductance than the second high inductance section 22.
  • the first low inductance section 11 and the second low inductance section 21 do not function as choke coils for signals of the third frequency.
  • the first middle inductance portion and the second middle inductance portion function as choke coils for signals of the first frequency and do not function as choke coils for signals of the second frequency and the third frequency.
  • the first high inductance section 12 and the second high inductance section 22 function as choke coils for signals of the third frequency.
  • the total electric length of the first low inductance portion 11 and the first middle inductance portion is 1/4 wavelength of the third frequency.
  • the example in which the antenna module 100 is used in the audio device 103 is shown, but it can also be used in other devices.
  • the antenna module 100 may be used in a television receiver or the like.
  • the present disclosure also includes a form realized by arbitrarily combining the components and functions in each embodiment without departing from the purpose of the present disclosure.
  • the multi-band antenna of the present disclosure can be used as a part of an array antenna for an antenna module used in, for example, an audio device.

Abstract

A multiband antenna (1) according to the invention is provided with: a board (40); an input terminal (16) to which signals are input; a conductive antenna part (10) connected to the input terminal (16) and having, in the order from the input terminal (16) side, a first low-inductance part (11), a first high-inductance part (12) in a meandering form, and a first front part (13) that are connected in series; and a conductive ground part (20) isolated from the input terminal (16) and having, in the order from the input terminal (16) side, a second low-inductance part (21), a second high-inductance part (22) in a meandering form, and a second front part (23) that are connected in series, wherein the electric length of the first low-inductance part (11) is one quarter-wavelength of a first frequency and wherein the sum of the electric lengths of the first low-inductance part (11), the first high-inductance part (12) and the first front part (13) is one quarter-wavelength of a second frequency.

Description

マルチバンドアンテナMulti-band antenna
　本開示は、マルチバンドアンテナに関する。 This disclosure relates to a multi-band antenna.
　近年、パソコン等の情報機器に加え、例えば、テレビ、音響装置などのような家電機器においても、無線ＬＡＮ（Local Area Network）、Ｂｌｕｅｔｏｏｔｈ（登録商標）などの規格に基づく無線端末が搭載され始めている。これに伴い、家電機器において、複数の規格にそれぞれ対応する複数の周波数帯域において無線通信を行うことがある。このような複数の周波数帯域における無線通信を行うためのアンテナを小型化するために、一つのアンテナで複数の周波数帯域の信号を送受信できるマルチバンドアンテナが提案されている（例えば、特許文献１など）。 In recent years, in addition to information devices such as personal computers, wireless terminals based on standards such as wireless LAN (Local Area Network) and Bluetooth (registered trademark) have begun to be installed in home appliances such as televisions and audio equipment. .. Along with this, in home appliances, wireless communication may be performed in a plurality of frequency bands corresponding to a plurality of standards. In order to miniaturize an antenna for performing wireless communication in such a plurality of frequency bands, a multi-band antenna capable of transmitting and receiving signals in a plurality of frequency bands with one antenna has been proposed (for example, Patent Document 1 and the like). ).
　特許文献１に記載されたデュアルバンドアンテナは、直線状体部と、ヘリカルコイル状部とを備える。このヘリカルコイル状部は、高い周波数帯域の信号に対しては、チョークコイルとして機能し、低い周波数帯域の信号に対しては、小型化されたアンテナの一部として機能する。これにより特許文献１では、小型で、かつ、周波数に応じて実効的な電気長を異ならせることができるデュアルバンドアンテナを実現しようとしている。 The dual band antenna described in Patent Document 1 includes a linear body portion and a helical coil-shaped portion. This helical coil-like portion functions as a choke coil for signals in a high frequency band, and functions as a part of a miniaturized antenna for signals in a low frequency band. As a result, Patent Document 1 attempts to realize a dual-band antenna that is compact and can have different effective electrical lengths depending on the frequency.
特開２０００－５９１３０号公報Japanese Unexamined Patent Publication No. 2000-59130
　本開示は、複数の周波数帯域において共振し、かつ、各周波数帯域において共振方向に対して垂直な指向性を実現できるマルチバンドアンテナを提供する。 The present disclosure provides a multi-band antenna that resonates in a plurality of frequency bands and can realize directivity perpendicular to the resonance direction in each frequency band.
　本開示の一態様に係るマルチバンドアンテナは、基板と、前記基板上に配置され、信号が入力される入力端子と、前記基板上に配置され、かつ、前記入力端子に接続されるアンテナ部であって、前記入力端子側から順に、直列に接続された第１低インダクタンス部、メアンダ形状を有する第１高インダクタンス部及び第１先端部を有する導電性のアンテナ部と、前記基板上に配置され、かつ、前記入力端子と絶縁される接地部であって、前記入力端子側から順に、直列に接続された第２低インダクタンス部、メアンダ形状を有する第２高インダクタンス部及び第２先端部を有する導電性の接地部とを備え、前記第１低インダクタンス部は、前記第１高インダクタンス部よりインダクタンスが低く、前記第２低インダクタンス部は、前記第２高インダクタンス部よりインダクタンスが低く、前記第１低インダクタンス部の電気長は、第１周波数の１／４波長であり、前記第１低インダクタンス部、前記第１高インダクタンス部及び前記第１先端部の電気長の和は、前記第１周波数より低い第２周波数の１／４波長である。 The multi-band antenna according to one aspect of the present disclosure includes a substrate, an input terminal arranged on the substrate and input with a signal, and an antenna portion arranged on the substrate and connected to the input terminal. The first low inductance portion connected in series, the first high inductance portion having a meander shape, and the conductive antenna portion having the first tip portion, which are connected in series from the input terminal side, are arranged on the substrate. A grounding portion that is insulated from the input terminal and has a second low inductance portion connected in series, a second high inductance portion having a meander shape, and a second tip portion in order from the input terminal side. The first low inductance section has a lower inductance than the first high inductance section, and the second low inductance section has a lower inductance than the second high inductance section, and the first low inductance section has a conductive grounding section. The electric length of the low inductance portion is 1/4 wavelength of the first frequency, and the sum of the electrical lengths of the first low inductance portion, the first high inductance portion, and the first tip portion is from the first frequency. It is a quarter wavelength of the lower second frequency.
　本開示に係るマルチバンドアンテナによれば、複数の周波数帯域において共振し、かつ、各周波数帯域において共振方向に対して垂直な指向性を実現できる。 According to the multi-band antenna according to the present disclosure, it is possible to resonate in a plurality of frequency bands and realize directivity perpendicular to the resonance direction in each frequency band.
図１は、実施の形態１に係るマルチバンドアンテナの構成を示す平面図である。FIG. 1 is a plan view showing the configuration of the multi-band antenna according to the first embodiment. 図２は、比較例に係るマルチバンドアンテナの構成を示す平面図である。FIG. 2 is a plan view showing the configuration of the multi-band antenna according to the comparative example. 図３は、実施の形態１に係るマルチバンドアンテナの第１周波数における指向性の概要を示す図である。FIG. 3 is a diagram showing an outline of directivity at the first frequency of the multi-band antenna according to the first embodiment. 図４は、比較例に係るマルチバンドアンテナの第１周波数における指向性の概要を示す図である。FIG. 4 is a diagram showing an outline of the directivity of the multi-band antenna according to the comparative example at the first frequency. 図５は、実施の形態１に係るマルチバンドアンテナの指向性のシミュレーション結果の一例を示すグラフである。FIG. 5 is a graph showing an example of a simulation result of the directivity of the multi-band antenna according to the first embodiment. 図６は、実施の形態１に係るマルチバンドアンテナの指向性のシミュレーション結果の他の一例を示すグラフである。FIG. 6 is a graph showing another example of the directivity simulation result of the multi-band antenna according to the first embodiment. 図７は、実施の形態１に係る接地部の幅と第２高インダクタンス部の各高インダクタンス要素の最小インダクタンス値との関係を示すグラフである。FIG. 7 is a graph showing the relationship between the width of the ground contact portion and the minimum inductance value of each high inductance element of the second high inductance portion according to the first embodiment. 図８は、実施の形態２に係るアンテナモジュールの構成を示す第１の平面図である。FIG. 8 is a first plan view showing the configuration of the antenna module according to the second embodiment. 図９は、実施の形態２に係るアンテナモジュールの構成を示す第２の平面図である。FIG. 9 is a second plan view showing the configuration of the antenna module according to the second embodiment. 図１０は、実施の形態２に係る３分配器の構成を示す平面図である。FIG. 10 is a plan view showing the configuration of the three distributors according to the second embodiment. 図１１は、実施の形態２に係るアレイアンテナの指向性を示すグラフである。FIG. 11 is a graph showing the directivity of the array antenna according to the second embodiment. 図１２は、実施の形態２に係るアレイアンテナの移相器の状態を変化させた場合の指向性を示すグラフである。FIG. 12 is a graph showing the directivity when the state of the phase shifter of the array antenna according to the second embodiment is changed. 図１３は、実施の形態２に係るアンテナモジュールを備える音響装置の構成を示す斜視図である。FIG. 13 is a perspective view showing the configuration of an audio device including the antenna module according to the second embodiment. 図１４は、実施の形態３に係るマルチバンドアンテナの構成を示す平面図である。FIG. 14 is a plan view showing the configuration of the multi-band antenna according to the third embodiment. 図１５は、実施の形態３に係るマルチバンドアンテナの指向性の第一のシミュレーション結果例を示すグラフである。FIG. 15 is a graph showing an example of the first simulation result of the directivity of the multi-band antenna according to the third embodiment. 図１６は、実施の形態３に係るマルチバンドアンテナの指向性の第二のシミュレーション結果例を示すグラフである。FIG. 16 is a graph showing an example of the second simulation result of the directivity of the multi-band antenna according to the third embodiment. 図１７は、実施の形態３に係る接地部の幅と第２高インダクタンス部の各高インダクタンス要素の最小インダクタンス値との関係を示すグラフである。FIG. 17 is a graph showing the relationship between the width of the ground contact portion and the minimum inductance value of each high inductance element of the second high inductance portion according to the third embodiment.
　以下、実施の形態について、図面を参照しながら具体的に説明する。 Hereinafter, the embodiment will be specifically described with reference to the drawings.
　なお、以下で説明する実施の形態は、いずれも包括的又は具体的な例を示すものである。以下の実施の形態で示される数値、形状、材料、構成要素、構成要素の配置位置及び接続形態、ステップ、ステップの順序などは、一例であり、本開示を限定する主旨ではない。 It should be noted that all of the embodiments described below show comprehensive or specific examples. Numerical values, shapes, materials, components, arrangement positions and connection forms of components, steps, order of steps, etc. shown in the following embodiments are examples, and are not intended to limit the present disclosure.
　また、各図は、模式図であり、必ずしも厳密に図示されたものではない。また、各図において、同じ構成部材については同じ符号を付している。 In addition, each figure is a schematic view and is not necessarily exactly illustrated. Further, in each figure, the same components are designated by the same reference numerals.
　（実施の形態１）
　実施の形態１に係るマルチバンドアンテナについて説明する。 (Embodiment 1)
The multi-band antenna according to the first embodiment will be described.
　［１－１．構成］
　まず、実施の形態１に係るマルチバンドアンテナの構成について、図１を用いて説明する。図１は、本実施の形態に係るマルチバンドアンテナ１の構成を示す平面図である。図１には、マルチバンドアンテナ１の基板４０の平面視における平面図が示されている。なお、図１において、マルチバンドアンテナ１の基板４０の主面４１に垂直な方向をＺ軸方向とし、Ｚ軸方向に垂直であって、互いに垂直な二つの方向をＸ軸方向及びＹ軸方向としている。 [1-1. Constitution]
First, the configuration of the multi-band antenna according to the first embodiment will be described with reference to FIG. FIG. 1 is a plan view showing the configuration of the multi-band antenna 1 according to the present embodiment. FIG. 1 shows a plan view of the substrate 40 of the multi-band antenna 1 in a plan view. In FIG. 1, the direction perpendicular to the main surface 41 of the substrate 40 of the multi-band antenna 1 is the Z-axis direction, and the two directions perpendicular to the Z-axis direction and perpendicular to each other are the X-axis direction and the Y-axis direction. It is said.
　マルチバンドアンテナ１は、複数の周波数帯域の信号を送受信するアンテナである。本実施の形態では、マルチバンドアンテナ１は、第１周波数を含む第１周波数帯域の信号と、第１周波数より低い第２周波数を含む第２周波数帯域の信号とを送受信する。第１周波数帯域及び第２周波数帯域は特に限定されないが、本実施の形態では、第１周波数帯域及び第２周波数帯域として、それぞれ、５ＧＨｚ帯及び２．４ＧＨｚ帯を用いる。これにより、マルチバンドアンテナ１を無線ＬＡＮの規格に基づく５ＧＨｚ帯及び２．４ＧＨｚ帯のデュアルバンドアンテナとして利用できる。図１に示されるように、マルチバンドアンテナ１は、基板４０と、入力端子１６と、アンテナ部１０と、接地部２０とを備える。本実施の形態では、マルチバンドアンテナ１は、さらに接地端子２６を備える。 The multi-band antenna 1 is an antenna that transmits and receives signals in a plurality of frequency bands. In the present embodiment, the multi-band antenna 1 transmits and receives a signal in the first frequency band including the first frequency and a signal in the second frequency band including the second frequency lower than the first frequency. The first frequency band and the second frequency band are not particularly limited, but in the present embodiment, the 5 GHz band and the 2.4 GHz band are used as the first frequency band and the second frequency band, respectively. As a result, the multi-band antenna 1 can be used as a dual-band antenna in the 5 GHz band and the 2.4 GHz band based on the wireless LAN standard. As shown in FIG. 1, the multi-band antenna 1 includes a substrate 40, an input terminal 16, an antenna portion 10, and a grounding portion 20. In the present embodiment, the multi-band antenna 1 further includes a ground terminal 26.
　基板４０は、マルチバンドアンテナ１の基台となる部材である。基板４０は、回路基板であり、基板４０の一方の主面４１に、アンテナ部１０及び接地部２０が配置される。本実施の形態では、基板４０は、矩形板状の誘電体である。基板４０は、例えば、ガラスエポキシ基板である。 The substrate 40 is a member that serves as a base for the multi-band antenna 1. The substrate 40 is a circuit board, and the antenna portion 10 and the grounding portion 20 are arranged on one main surface 41 of the substrate 40. In the present embodiment, the substrate 40 is a rectangular plate-shaped dielectric. The substrate 40 is, for example, a glass epoxy substrate.
　入力端子１６は、基板４０上に配置され、信号が入力される端子である。本実施の形態では、入力端子１６には、マルチバンドアンテナ１が送信する高周波信号が入力される。また、入力端子１６は、マルチバンドアンテナ１が受信した高周波信号を出力する出力端子としても機能する。入力端子１６には、例えば、基板４０の主面４１の裏側の主面から基板４０を貫通するビア配線を介して信号が入力される。また、入力端子１６は、アンテナ部１０に接続される。 The input terminal 16 is a terminal arranged on the board 40 to input a signal. In the present embodiment, the high frequency signal transmitted by the multi-band antenna 1 is input to the input terminal 16. The input terminal 16 also functions as an output terminal that outputs a high-frequency signal received by the multi-band antenna 1. A signal is input to the input terminal 16 from, for example, a main surface on the back side of the main surface 41 of the substrate 40 via a via wiring penetrating the substrate 40. Further, the input terminal 16 is connected to the antenna unit 10.
　接地端子２６は、基板４０上に配置され、グランドに接続される端子である。本実施の形態では、接地端子２６は、基板４０の主面４１に配置され、接地部２０に接続される。接地端子２６は、例えば、基板４０を貫通するビア配線を介してグランドに接続される。接地端子２６の個数は特に限定されないが、本実施の形態では、２個である。 The ground terminal 26 is a terminal arranged on the board 40 and connected to the ground. In the present embodiment, the ground terminal 26 is arranged on the main surface 41 of the substrate 40 and is connected to the ground portion 20. The ground terminal 26 is connected to the ground via, for example, a via wiring penetrating the substrate 40. The number of ground terminals 26 is not particularly limited, but is two in the present embodiment.
　アンテナ部１０は、基板４０上に配置され、入力端子１６に接続される導電性部材である。本実施の形態では、アンテナ部１０において第１周波数帯域の信号及び第２周波数帯域の信号が共振する。これにより、アンテナ部１０から電波が放射される。アンテナ部１０は、入力端子１６側から順に、直列に接続された第１低インダクタンス部１１、第１高インダクタンス部１２及び第１先端部１３を有する。第１低インダクタンス部１１、第１高インダクタンス部１２及び第１先端部１３の電気長の和は、第２周波数の１／４波長である。これにより、アンテナ部１０において第２周波数を含む第２周波数帯域の信号が共振する。 The antenna portion 10 is a conductive member arranged on the substrate 40 and connected to the input terminal 16. In the present embodiment, the signal in the first frequency band and the signal in the second frequency band resonate in the antenna unit 10. As a result, radio waves are radiated from the antenna unit 10. The antenna portion 10 has a first low inductance portion 11, a first high inductance portion 12, and a first tip portion 13 connected in series from the input terminal 16 side. The sum of the electrical lengths of the first low inductance portion 11, the first high inductance portion 12, and the first tip portion 13 is 1/4 wavelength of the second frequency. As a result, the signal in the second frequency band including the second frequency resonates in the antenna unit 10.
　アンテナ部１０が入力端子１６に接続される位置は特に限定されないが、本実施の形態では、入力端子１６は、第１低インダクタンス部１１の接地部２０側の端部に配置される。より詳しくは、入力端子１６は、第１低インダクタンス部１１の接地部２０側の端部のみに配置され、第１高インダクタンス部１２及び第１先端部１３には配置されない。なお、第１低インダクタンス部１１の端部とは、例えば、第１低インダクタンス部１１の接地部２０側の端から、第１低インダクタンス部１１のＹ軸方向における長さの１０％以下の範囲の領域を意味する。 The position where the antenna portion 10 is connected to the input terminal 16 is not particularly limited, but in the present embodiment, the input terminal 16 is arranged at the end of the first low inductance portion 11 on the grounding portion 20 side. More specifically, the input terminal 16 is arranged only at the end portion of the first low inductance portion 11 on the grounding portion 20 side, and is not arranged at the first high inductance portion 12 and the first tip portion 13. The end of the first low inductance portion 11 is, for example, a range of 10% or less of the length of the first low inductance portion 11 in the Y-axis direction from the end of the first low inductance portion 11 on the grounding portion 20 side. Means the area of.
　本実施の形態では、アンテナ部１０は、基板４０の主面４１上にパターニングされた導電性部材であり、例えば、銅膜などの金属膜で形成される。また、第１低インダクタンス部１１、第１高インダクタンス部１２及び第１先端部１３は、図１のＹ軸方向に配列される。これにより、図１のＹ軸方向が、アンテナ部１０の長手方向、及び、アンテナ部１０における信号の共振方向となる。図１に示されるように、第１低インダクタンス部１１、第１高インダクタンス部１２及び第１先端部１３の幅（つまり、共振方向に垂直な方向であって、基板４０の主面４１に平行な方向の寸法）は、同一である。 In the present embodiment, the antenna portion 10 is a conductive member patterned on the main surface 41 of the substrate 40, and is formed of, for example, a metal film such as a copper film. Further, the first low inductance portion 11, the first high inductance portion 12, and the first tip portion 13 are arranged in the Y-axis direction of FIG. As a result, the Y-axis direction in FIG. 1 becomes the longitudinal direction of the antenna portion 10 and the resonance direction of the signal in the antenna portion 10. As shown in FIG. 1, the widths of the first low inductance portion 11, the first high inductance portion 12, and the first tip portion 13 (that is, the direction perpendicular to the resonance direction and parallel to the main surface 41 of the substrate 40). Dimensions) are the same.
　第１低インダクタンス部１１は、アンテナ部１０のうち、入力端子１６に接続される部分である。第１低インダクタンス部１１の一方の端部に入力端子１６が接続され、他方の端部に第１高インダクタンス部１２が接続される。第１低インダクタンス部１１の電気長は、第１周波数の１／４波長である。第１低インダクタンス部１１は、第１高インダクタンス部１２より低いインダクタンスを有する。本実施の形態では、図１に示されるように、第１低インダクタンス部１１は、メアンダ（meander）形状を有するが、第１周波数帯域及び第２周波数帯域の信号に対してチョークコイルとして機能しない（つまり、信号を阻止しない）程度に低いインダクタンスを有する。このように、第１低インダクタンス部１１がメアンダ形状を有することにより、第１低インダクタンス部１１の共振方向（つまり、図１におけるＹ軸方向）の寸法を低減できる。 The first low inductance portion 11 is a portion of the antenna portion 10 connected to the input terminal 16. The input terminal 16 is connected to one end of the first low inductance portion 11, and the first high inductance portion 12 is connected to the other end. The electrical length of the first low inductance portion 11 is 1/4 wavelength of the first frequency. The first low inductance section 11 has a lower inductance than the first high inductance section 12. In the present embodiment, as shown in FIG. 1, the first low inductance portion 11 has a meander shape, but does not function as a choke coil for signals in the first frequency band and the second frequency band. It has a low inductance (that is, it does not block the signal). As described above, since the first low inductance portion 11 has a meander shape, the dimension of the first low inductance portion 11 in the resonance direction (that is, the Y-axis direction in FIG. 1) can be reduced.
　第１高インダクタンス部１２は、アンテナ部１０のうち、第１低インダクタンス部１１と第１先端部１３との間に配置される部分であり、メアンダ形状を有する。第１高インダクタンス部１２は、第１低インダクタンス部１１より高いインダクタンスを有する。本実施の形態では、第１高インダクタンス部１２のメアンダ形状は、第１低インダクタンス部１１のメアンダ形状より、線幅及び間隔が小さい。これにより、第１高インダクタンス部１２のインダクタンスが第１低インダクタンス部１１より高くなる。本実施の形態では、第１高インダクタンス部１２は、線幅０．１ｍｍ、間隔０．１ｍｍ、長さ（図１におけるＹ軸方向の寸法）２．１ｍｍ、幅（図１におけるＸ軸方向の寸法）３ｍｍのメアンダ形状を有する。第１高インダクタンス部１２は、第１周波数帯域の信号に対してチョークコイルとして機能する。つまり、第１低インダクタンス部１１に接続される入力端子１６から入力された第１周波数帯域の信号に対するアンテナ部１０の実効的な電気長は、第１低インダクタンス部１１の電気長（第１周波数の１／４波長）となる。したがって、アンテナ部１０において、第１周波数帯域の信号が共振する。なお、第１高インダクタンス部１２は、第２周波数帯域の信号に対してチョークコイルとして機能しない程度に低いインダクタンスを有する。このため、第１高インダクタンス部１２は、第２周波数帯域の信号を阻止しない。したがって、第２周波数帯域の信号は、アンテナ部１０の第１低インダクタンス部１１、第１高インダクタンス部１２及び第１先端部１３からなる経路において共振する。 The first high inductance portion 12 is a portion of the antenna portion 10 that is arranged between the first low inductance portion 11 and the first tip portion 13, and has a meander shape. The first high inductance section 12 has a higher inductance than the first low inductance section 11. In the present embodiment, the meander shape of the first high inductance portion 12 has a smaller line width and spacing than the meander shape of the first low inductance portion 11. As a result, the inductance of the first high inductance section 12 becomes higher than that of the first low inductance section 11. In the present embodiment, the first high inductance portion 12 has a line width of 0.1 mm, an interval of 0.1 mm, a length (dimension in the Y-axis direction in FIG. 1) of 2.1 mm, and a width (in the X-axis direction in FIG. 1). Dimensions) It has a meander shape of 3 mm. The first high inductance unit 12 functions as a choke coil for signals in the first frequency band. That is, the effective electric length of the antenna unit 10 with respect to the signal of the first frequency band input from the input terminal 16 connected to the first low inductance unit 11 is the electric length of the first low inductance unit 11 (first frequency). 1/4 wavelength). Therefore, in the antenna unit 10, the signal in the first frequency band resonates. The first high inductance unit 12 has a low inductance that does not function as a choke coil with respect to a signal in the second frequency band. Therefore, the first high inductance unit 12 does not block the signal in the second frequency band. Therefore, the signal in the second frequency band resonates in the path including the first low inductance portion 11, the first high inductance portion 12, and the first tip portion 13 of the antenna portion 10.
　第１先端部１３は、アンテナ部１０のうち、入力端子１６から共振方向に最も離れた端部に配置された部分である。第１先端部１３の形状は特に限定されないが、本実施の形態では矩形状である。これにより、例えば、第１先端部１３をメアンダ形状とする場合より第１先端部１３における電流密度を高めることができるため、第１先端部１３からの電波の放射効率を高めることができる。 The first tip portion 13 is a portion of the antenna portion 10 arranged at the end portion farthest from the input terminal 16 in the resonance direction. The shape of the first tip portion 13 is not particularly limited, but is rectangular in the present embodiment. As a result, for example, the current density at the first tip portion 13 can be increased as compared with the case where the first tip portion 13 has a meander shape, so that the radiation efficiency of radio waves from the first tip portion 13 can be increased.
　接地部２０は、基板４０上に配置され、入力端子１６と絶縁される導電性部材である。接地部２０は、アンテナ部１０に対して、共振方向に所定の距離だけ離隔して配置されている。アンテナ部１０と接地部２０との間隔は、例えば、０より大きく、１ｍｍ程度以下である。本実施の形態では、アンテナ部１０と接地部２０との間隔は、０．５ｍｍである。また、接地部２０の幅（つまり、共振方向に垂直な方向であって、基板４０の主面４１に平行な方向の寸法）は、アンテナ部１０の幅より広い。 The grounding portion 20 is a conductive member arranged on the substrate 40 and insulated from the input terminal 16. The grounding portion 20 is arranged at a distance of a predetermined distance from the antenna portion 10 in the resonance direction. The distance between the antenna portion 10 and the grounding portion 20 is, for example, greater than 0 and less than or equal to about 1 mm. In the present embodiment, the distance between the antenna portion 10 and the grounding portion 20 is 0.5 mm. Further, the width of the grounding portion 20 (that is, the dimension in the direction perpendicular to the resonance direction and parallel to the main surface 41 of the substrate 40) is wider than the width of the antenna portion 10.
　接地部２０は、入力端子１６側から順に、直列に接続された第２低インダクタンス部２１、第２高インダクタンス部２２及び第２先端部２３を有する。本実施の形態では、接地部２０は、基板４０の主面４１上にパターニングされた導電性部材であり、例えば、銅膜などの金属膜で形成される。また、第２低インダクタンス部２１、第２高インダクタンス部２２及び第２先端部２３は、図１のＹ軸方向に配列される。 The grounding portion 20 has a second low inductance portion 21, a second high inductance portion 22, and a second tip portion 23 connected in series from the input terminal 16 side. In the present embodiment, the grounding portion 20 is a conductive member patterned on the main surface 41 of the substrate 40, and is formed of, for example, a metal film such as a copper film. Further, the second low inductance portion 21, the second high inductance portion 22, and the second tip portion 23 are arranged in the Y-axis direction of FIG.
　第２低インダクタンス部２１、第２高インダクタンス部２２及び第２先端部２３の電気長の合計は、アンテナ部１０から放射される第２周波数の電波の指向性が、アンテナ部１０の長手方向（つまり、図１のＹ軸方向）に垂直な面（つまり、図１のＺＸ平面に平行な面）に沿って広がるように設定されている。当該電気長の合計と第２周波数の電波の指向性との関係は、例えば、シミュレーションなどによって求めることができる。 The total electric length of the second low inductance portion 21, the second high inductance portion 22, and the second tip portion 23 is such that the directivity of the second frequency radio wave radiated from the antenna portion 10 is the longitudinal direction of the antenna portion 10 ( That is, it is set to spread along a plane perpendicular to the Y-axis direction of FIG. 1 (that is, a plane parallel to the ZX plane of FIG. 1). The relationship between the total electric length and the directivity of the radio wave of the second frequency can be obtained by, for example, simulation.
　接地部２０は、接地端子２６と接続される。接地端子２６の配置は特に限定されないが、本実施の形態では、接地端子２６は、第２低インダクタンス部２１のアンテナ部１０側（つまり、入力端子１６側）の端部に配置される。より詳しくは、二つの接地端子２６は、第２低インダクタンス部２１のアンテナ部１０側の端部のみに配置され、第２高インダクタンス部２２及び第２先端部２３には配置されない。なお、第２低インダクタンス部２１の端部とは、例えば、第２低インダクタンス部２１のアンテナ部１０側の端から、第２低インダクタンス部２１の共振方向（図１のＹ軸方向）における長さの１０％以下の範囲の領域を意味する。 The grounding portion 20 is connected to the grounding terminal 26. The arrangement of the ground terminal 26 is not particularly limited, but in the present embodiment, the ground terminal 26 is arranged at the end of the second low inductance portion 21 on the antenna portion 10 side (that is, the input terminal 16 side). More specifically, the two ground terminals 26 are arranged only at the end of the second low inductance portion 21 on the antenna portion 10 side, and are not arranged at the second high inductance portion 22 and the second tip portion 23. The end of the second low inductance portion 21 is, for example, the length of the second low inductance portion 21 in the resonance direction (Y-axis direction in FIG. 1) from the end of the second low inductance portion 21 on the antenna portion 10 side. It means an area in the range of 10% or less of the inductance.
　第２低インダクタンス部２１は、接地部２０のうち、アンテナ部１０に最も近い位置に配置される部分である。第２低インダクタンス部２１の一方の端部に接地端子２６が接続され、他方の端部に第２高インダクタンス部２２が接続される。第２低インダクタンス部２１の電気長は、アンテナ部１０から放射される第１周波数の電波の指向性が、アンテナ部１０の長手方向に垂直な面に沿って広がるように設定されている。第２低インダクタンス部２１の電気長と第１周波数の電波の指向性との関係は、例えば、シミュレーションなどによって求めることができる。 The second low inductance portion 21 is a portion of the grounding portion 20 that is arranged at the position closest to the antenna portion 10. The ground terminal 26 is connected to one end of the second low inductance portion 21, and the second high inductance portion 22 is connected to the other end. The electrical length of the second low inductance section 21 is set so that the directivity of the first frequency radio wave radiated from the antenna section 10 spreads along a plane perpendicular to the longitudinal direction of the antenna section 10. The relationship between the electric length of the second low inductance portion 21 and the directivity of the radio wave of the first frequency can be obtained by, for example, simulation.
　第２低インダクタンス部２１は、第２高インダクタンス部２２より低いインダクタンスを有する。本実施の形態では、図１に示されるように、第２低インダクタンス部２１は、矩形状の形状を有するが、第２低インダクタンス部２１の形状は、これに限定されない。第２低インダクタンス部２１の形状は、第２低インダクタンス部２１のインダクタンスが、第１周波数及び第２周波数の信号に対してチョークコイルとして機能しない程度に低いインダクタンスを有するように設計されていればよい。 The second low inductance section 21 has a lower inductance than the second high inductance section 22. In the present embodiment, as shown in FIG. 1, the second low inductance portion 21 has a rectangular shape, but the shape of the second low inductance portion 21 is not limited to this. The shape of the second low inductance portion 21 is designed so that the inductance of the second low inductance portion 21 has such a low inductance that it does not function as a choke coil with respect to the signals of the first frequency and the second frequency. Good.
　第２高インダクタンス部２２は、接地部２０のうち、第２低インダクタンス部２１と第２先端部２３との間に配置される部分であり、メアンダ形状を有する。第２高インダクタンス部２２は、第２低インダクタンス部２１より高いインダクタンスを有する。第２高インダクタンス部２２は、第１周波数帯域の信号に対してチョークコイルとして機能する。つまり、第２低インダクタンス部２１に誘起される第１周波数帯域の信号に対する接地部２０の実効的な電気長は、第２低インダクタンス部２１の電気長となる。また、第２高インダクタンス部２２は、第２周波数帯域の信号に対してチョークコイルとして機能しない程度に低いインダクタンスを有する。このため、第２高インダクタンス部２２は、第２周波数帯域の信号を阻止しない。したがって、第２周波数帯域の信号に対する接地部２０の実効的な電気長は、接地部２０の第２高インダクタンス部２２を含む経路の電気長を含む。 The second high inductance portion 22 is a portion of the grounding portion 20 that is arranged between the second low inductance portion 21 and the second tip portion 23, and has a meander shape. The second high inductance section 22 has a higher inductance than the second low inductance section 21. The second high inductance unit 22 functions as a choke coil for signals in the first frequency band. That is, the effective electrical length of the grounding portion 20 with respect to the signal in the first frequency band induced in the second low inductance portion 21 is the electrical length of the second low inductance portion 21. Further, the second high inductance unit 22 has a low inductance that does not function as a choke coil with respect to a signal in the second frequency band. Therefore, the second high inductance unit 22 does not block the signal in the second frequency band. Therefore, the effective electrical length of the grounding portion 20 with respect to the signal in the second frequency band includes the electrical length of the path including the second high inductance portion 22 of the grounding portion 20.
　第２高インダクタンス部２２は、第２低インダクタンス部２１の幅方向（図１のＸ軸方向）の両端にそれぞれ接続される二つの高インダクタンス要素２２ａ及び２２ｂを有する。二つの高インダクタンス要素２２ａ及び２２ｂの間には、開口２２ｃが形成されている。つまり、二つの高インダクタンス要素２２ａ及び２２ｂの間には、導電性部材が配置されない領域が形成される。なお、基板４０の開口２２ｃに対応する領域には、開口は設けられなくてもよい。二つの高インダクタンス要素２２ａ及び２２ｂの各々は、メアンダ形状を有する。また、二つの高インダクタンス要素２２ａ及び２２ｂは、互いに左右反転した構造を有する。したがって、二つの高インダクタンス要素２２ａ及び２２ｂの電気長は等しい。なお、本実施の形態では、マルチバンドアンテナ１の第２高インダクタンス部２２の電気長を、二つの高インダクタンス要素２２ａ及び２２ｂの一方の電気長と定義する。また、二つの高インダクタンス要素２２ａ及び２２ｂのメアンダ形状部分における線幅及びピッチは、それぞれ、アンテナ部１０の第１高インダクタンス部１２のメアンダ形状部分における線幅及びピッチと同一であってもよい。これにより、マルチバンドアンテナ１の設計を容易化できる。 The second high inductance section 22 has two high inductance elements 22a and 22b connected to both ends of the second low inductance section 21 in the width direction (X-axis direction in FIG. 1), respectively. An opening 22c is formed between the two high inductance elements 22a and 22b. That is, a region in which the conductive member is not arranged is formed between the two high inductance elements 22a and 22b. The region corresponding to the opening 22c of the substrate 40 may not be provided with an opening. Each of the two high inductance elements 22a and 22b has a meander shape. Further, the two high inductance elements 22a and 22b have a structure that is horizontally inverted from each other. Therefore, the electrical lengths of the two high inductance elements 22a and 22b are equal. In the present embodiment, the electric length of the second high inductance portion 22 of the multi-band antenna 1 is defined as the electric length of one of the two high inductance elements 22a and 22b. Further, the line width and pitch of the two high inductance elements 22a and 22b in the meander-shaped portion may be the same as the line width and pitch of the first high-inductance portion 12 of the antenna portion 10 in the meander-shaped portion, respectively. This makes it possible to facilitate the design of the multi-band antenna 1.
　第２低インダクタンス部２１においては、図１の破線の矢印で示されるように、主に、第２低インダクタンス部２１の端縁に沿って、送受信する電波に対応する電流が流れる。このため、二つの高インダクタンス要素２２ａ及び２２ｂを接地部２０の幅方向の端部に配置することにより、図１の破線の矢印で示される電流は、高インダクタンス要素２２ａ及び高インダクタンス要素２２ｂのいずれかを通る。 In the second low-inductance section 21, as shown by the broken line arrow in FIG. 1, a current corresponding to the radio waves transmitted and received mainly flows along the edge of the second low-inductance section 21. Therefore, by arranging the two high inductance elements 22a and 22b at the widthwise ends of the grounding portion 20, the current indicated by the broken line arrow in FIG. 1 is either the high inductance element 22a or the high inductance element 22b. Pass through.
　第２先端部２３は、接地部２０のうち、アンテナ部１０から共振方向に最も離れた端部に配置された部分である。第２先端部２３の形状は特に限定されないが、本実施の形態では、第２先端部２３は、矩形状の形状を有する。また、第２先端部２３は、第２高インダクタンス部２２の二つの高インダクタンス要素２２ａ及び２２ｂを接続する。これにより、第２先端部２３において、二つの高インダクタンス要素２２ａ及び２２ｂから第２先端部２３に流れ込む電流成分を相殺できるため、これらの電流成分に起因する共振方向に広がる電波の放射を抑制できる。 The second tip portion 23 is a portion of the grounding portion 20 arranged at the end portion farthest from the antenna portion 10 in the resonance direction. The shape of the second tip portion 23 is not particularly limited, but in the present embodiment, the second tip portion 23 has a rectangular shape. Further, the second tip portion 23 connects the two high inductance elements 22a and 22b of the second high inductance portion 22. As a result, in the second tip portion 23, the current components flowing from the two high inductance elements 22a and 22b into the second tip portion 23 can be canceled out, so that the radiation of radio waves spreading in the resonance direction due to these current components can be suppressed. ..
　［１－２．作用及び効果］
　次に、本実施の形態に係るマルチバンドアンテナ１の作用及び効果について、比較例に係るマルチバンドアンテナと比較しながら図２～図４を用いて説明する。図２は、比較例に係るマルチバンドアンテナ１００１の構成を示す平面図である。図２には、比較例に係るマルチバンドアンテナ１００１の基板４０の平面視における平面図が示されている。図３及び図４は、それぞれ、本実施の形態及び比較例に係るマルチバンドアンテナの第１周波数における指向性の概要を示す図である。 [1-2. Action and effect]
Next, the operation and effect of the multi-band antenna 1 according to the present embodiment will be described with reference to FIGS. 2 to 4 while comparing with the multi-band antenna according to the comparative example. FIG. 2 is a plan view showing the configuration of the multi-band antenna 1001 according to the comparative example. FIG. 2 shows a plan view of the substrate 40 of the multi-band antenna 1001 according to the comparative example in a plan view. 3 and 4 are diagrams showing an outline of the directivity of the multi-band antenna according to the present embodiment and the comparative example at the first frequency, respectively.
　図２に示される比較例に係るマルチバンドアンテナ１００１は、本実施の形態に係るマルチバンドアンテナ１と同様に、基板４０と、入力端子１６と、接地端子２６と、アンテナ部１０と、接地部１０２０とを備える。比較例に係るマルチバンドアンテナ１００１は、接地部１０２０の構成において、本実施の形態に係るマルチバンドアンテナ１と相違し、その他の点において一致する。比較例に係る接地部１０２０は、本実施の形態に係る接地部２０全体の電気長と同等の電気長を有する。ただし、比較例に係る接地部１０２０は、平板状の形状を有する。言い換えると、比較例に係る接地部１０２０は、その全体において、本実施の形態に係る接地部２０の第２低インダクタンス部２１と同様の構成を有する。 The multi-band antenna 1001 according to the comparative example shown in FIG. 2 has a substrate 40, an input terminal 16, a ground terminal 26, an antenna portion 10, and a ground portion, similarly to the multi-band antenna 1 according to the present embodiment. It is equipped with 1020. The multi-band antenna 1001 according to the comparative example is different from the multi-band antenna 1 according to the present embodiment in the configuration of the grounding portion 1020, and is consistent in other respects. The grounding portion 1020 according to the comparative example has an electric length equivalent to the electric length of the entire grounding portion 20 according to the present embodiment. However, the ground contact portion 1020 according to the comparative example has a flat plate shape. In other words, the grounding portion 1020 according to the comparative example has the same configuration as the second low inductance portion 21 of the grounding portion 20 according to the present embodiment as a whole.
　第２周波数の信号に関し、本実施の形態に係るマルチバンドアンテナ１においては、アンテナ部１０から放射される第２周波数の電波の指向性が、アンテナ部１０の長手方向に垂直な面に沿って広がるように、接地部２０全体の電気長が設定されている。比較例に係る接地部１０２０も本実施の形態に係る接地部２０と同等の電気長を有するため、比較例に係るマルチバンドアンテナ１００１においても、アンテナ部１０から放射される第２周波数の電波の指向性は、アンテナ部１０の長手方向に垂直な面に沿って広がる。 Regarding the signal of the second frequency, in the multi-band antenna 1 according to the present embodiment, the directivity of the radio wave of the second frequency radiated from the antenna portion 10 is along the plane perpendicular to the longitudinal direction of the antenna portion 10. The electric length of the entire ground contact portion 20 is set so as to spread. Since the grounding portion 1020 according to the comparative example also has an electric length equivalent to that of the grounding portion 20 according to the present embodiment, the multi-band antenna 1001 according to the comparative example also has a second frequency radio wave radiated from the antenna portion 10. The directivity extends along a plane perpendicular to the longitudinal direction of the antenna portion 10.
　一方、第１周波数の信号に関して、本実施の形態に係るマルチバンドアンテナ１は、第１周波数の信号に対してチョークコイルとして機能する第２高インダクタンス部２２を備えるため、第２低インダクタンス部２１に誘起される第１周波数の信号に対しては、接地部２０の実効的な電気長は、第２低インダクタンス部２１の電気長と等しくなる。そして、第２低インダクタンス部２１の電気長は、アンテナ部１０から放射される第１周波数の電波の指向性が、アンテナ部１０の長手方向に垂直な面に沿って広がるように設定されている。このため、図３に示されるように、第１周波数の電波の指向性が、アンテナ部１０の長手方向に垂直な面に沿って広がる。 On the other hand, regarding the signal of the first frequency, the multi-band antenna 1 according to the present embodiment includes the second high inductance section 22 which functions as a choke coil with respect to the signal of the first frequency, so that the second low inductance section 21 For the first frequency signal induced in, the effective electrical length of the grounding section 20 is equal to the electrical length of the second low inductance section 21. The electrical length of the second low inductance section 21 is set so that the directivity of the first frequency radio wave radiated from the antenna section 10 spreads along a plane perpendicular to the longitudinal direction of the antenna section 10. .. Therefore, as shown in FIG. 3, the directivity of the radio wave of the first frequency spreads along the plane perpendicular to the longitudinal direction of the antenna portion 10.
　これに対して、比較例に係るマルチバンドアンテナ１００１は、第２高インダクタンス部２２を有さないため、第１周波数の信号に対する電気長は、第２周波数に対する電気長と同様に接地部１０２０全体の電気長と等しくなる。このような構成を有するマルチバンドアンテナ１００１においては、図４に示されるように、第１周波数の電波の指向性が、アンテナ部１０の長手方向に垂直な面に対して、接地部２０寄りに斜め方向に（つまり、図４において斜め下向きに）広がる。なお、図４では、ＸＹ平面に平行な面内の指向性だけが示されているが、マルチバンドアンテナ１００１の入力端子１６を通り、Ｙ軸に平行なすべての面内において、マルチバンドアンテナ１００１の指向性は、図４と同様の指向性となる。これは、比較例に係るマルチバンドアンテナ１００１において、本実施の形態に係るマルチバンドアンテナ１より、第１周波数の信号に対する接地部１０２０の実効的な電気長が長くなることで、接地部１０２０の先端部へ流れ込む電流により発生する電界成分が、アンテナ部１０で発生する電界成分よりも強くなることに起因すると考えられる。 On the other hand, since the multi-band antenna 1001 according to the comparative example does not have the second high inductance portion 22, the electric length for the signal of the first frequency is the same as the electric length for the second frequency, and the entire grounding portion 1020. Is equal to the electrical length of. In the multi-band antenna 1001 having such a configuration, as shown in FIG. 4, the directivity of the radio wave of the first frequency is closer to the grounding portion 20 with respect to the plane perpendicular to the longitudinal direction of the antenna portion 10. It spreads diagonally (that is, diagonally downward in FIG. 4). Although only the directivity in the plane parallel to the XY plane is shown in FIG. 4, the multi-band antenna 1001 passes through the input terminal 16 of the multi-band antenna 1001 and is parallel to the Y axis in all the planes. The directivity of is the same as that of FIG. This is because, in the multi-band antenna 1001 according to the comparative example, the effective electric length of the grounding portion 1020 with respect to the signal of the first frequency is longer than that of the multi-band antenna 1 according to the present embodiment, so that the grounding portion 1020 It is considered that this is because the electric field component generated by the current flowing into the tip portion becomes stronger than the electric field component generated by the antenna portion 10.
　以上のように、本実施の形態に係るマルチバンドアンテナ１においては、接地部２０が、メアンダ形状を有する第２高インダクタンス部２２を有することで、第１周波数に対する接地部２０の実効的な電気長を第２周波数の信号に対する実効的な電気長より短くすることができる。したがって、第１周波数及び第２周波数の各信号に対する接地部２０の実効的な電気長を適切に設定することで、各周波数が含まれる周波数帯域において共振方向に対して垂直な指向性を実現できる。 As described above, in the multi-band antenna 1 according to the present embodiment, the grounding portion 20 has the second high inductance portion 22 having a meander shape, so that the effective electricity of the grounding portion 20 with respect to the first frequency is obtained. The length can be shorter than the effective electrical length for the second frequency signal. Therefore, by appropriately setting the effective electric length of the grounding portion 20 for each signal of the first frequency and the second frequency, it is possible to realize the directivity perpendicular to the resonance direction in the frequency band including each frequency. ..
　このようなマルチバンドアンテナ１は、例えば、アレイアンテナにおいて用いる場合に特に有効である。つまり、マルチバンドアンテナ１は、共振方向に垂直な指向性を有するため、複数のマルチバンドアンテナ１を共振方向に垂直な方向に配列してアレイアンテナを構成する場合に、各マルチバンドアンテナが放射する電波間の相互作用を高めることができる。 Such a multi-band antenna 1 is particularly effective when used in an array antenna, for example. That is, since the multi-band antenna 1 has a directivity perpendicular to the resonance direction, each multi-band antenna radiates when a plurality of multi-band antennas 1 are arranged in a direction perpendicular to the resonance direction to form an array antenna. It is possible to enhance the interaction between the radio waves.
　［１－３．シミュレーション結果］
　次に、本実施の形態に係るマルチバンドアンテナ１のシミュレーション結果について図５～図７を用いて説明する。図５及び図６は、本実施の形態に係るマルチバンドアンテナ１の指向性のシミュレーション結果例を示すグラフである。図５及び図６には、それぞれ、第２高インダクタンス部２２の各高インダクタンス要素のインダクタンスを６ｎＨ及び７ｎＨとした場合のシミュレーション結果が示されている。また、本シミュレーションにおいては、接地部２０の幅Ｗｇ（つまり、共振方向に垂直な方向であって、基板４０の主面４１に平行な方向の寸法）を７ｍｍとしている。各図においては、入力端子１６に入力する第１周波数帯域の信号の周波数を、５．０ＧＨｚ、５．２ＧＨｚ、５．４ＧＨｚ、５．６ＧＨｚ、５．８ＧＨｚ及び６．０ＧＨｚとした各場合の指向性が示されている。なお、各図における角度θｙｘは、各図中のＹ軸方向からＸ軸方向に向かって傾斜する角度を示す。 [1-3. simulation result]
Next, the simulation results of the multi-band antenna 1 according to the present embodiment will be described with reference to FIGS. 5 to 7. 5 and 6 are graphs showing an example of a simulation result of directivity of the multi-band antenna 1 according to the present embodiment. 5 and 6 show simulation results when the inductance of each high inductance element of the second high inductance portion 22 is 6 nH and 7 nH, respectively. Further, in this simulation, the width Wg of the ground contact portion 20 (that is, the dimension in the direction perpendicular to the resonance direction and parallel to the main surface 41 of the substrate 40) is set to 7 mm. In each figure, the directivity in each case where the frequency of the signal of the first frequency band input to the input terminal 16 is 5.0 GHz, 5.2 GHz, 5.4 GHz, 5.6 GHz, 5.8 GHz, and 6.0 GHz. The sex is shown. The angle θyx in each figure indicates an angle of inclination from the Y-axis direction to the X-axis direction in each figure.
　図５に示されるように、各高インダクタンス要素のインダクタンスが６ｎＨの場合、周波数５．２ＧＨｚ～６ＧＨｚの信号に対して、共振方向に対して垂直な指向性を概ね実現できているが、周波数５．０ＧＨｚの信号に対して、共振方向に対して垂直な指向性を実現できない。これは、周波数５．０ＧＨｚの信号に対しては、各高インダクタンス要素のチョークコイルとしての機能が十分に働かなかったことに起因すると考えられる。また、各高インダクタンス要素のインダクタンスが６ｎＨ未満の場合についても同様のシミュレーションを行ったところ、周波数５．０ＧＨｚ～６ＧＨｚの信号の少なくとも一部に対して、共振方向に対して垂直な指向性を実現できなかった。 As shown in FIG. 5, when the inductance of each high inductance element is 6 nH, directivity perpendicular to the resonance direction can be generally realized for a signal having a frequency of 5.2 GHz to 6 GHz, but the frequency 5 Directivity perpendicular to the resonance direction cannot be realized for a 0.0 GHz signal. It is considered that this is because the function of each high inductance element as a choke coil did not work sufficiently for a signal having a frequency of 5.0 GHz. Further, when the same simulation was performed when the inductance of each high inductance element was less than 6 nH, directivity perpendicular to the resonance direction was realized for at least a part of the signal having a frequency of 5.0 GHz to 6 GHz. could not.
　一方、図６に示されるように、各高インダクタンス要素のインダクタンスが７ｎＨの場合、５．０ＧＨｚ以上６ＧＨｚ以下のすべての信号に対して、共振方向に対して垂直な指向性を実現できる。また、各高インダクタンス要素のインダクタンスが７ｎＨより大きい場合についても同様のシミュレーションを行ったところ、周波数５．０ＧＨｚ～６ＧＨｚのすべての信号に対して、共振方向に対して垂直な指向性を実現できた。以上のことから、第１周波数帯域として、５．０ＧＨｚ以上６ＧＨｚ以下の周波数帯域を採用し、接地部２０の幅Ｗｇが７ｍｍの場合には、各高インダクタンス要素のインダクタンスは、７ｎＨ以上である必要があることがわかる。 On the other hand, as shown in FIG. 6, when the inductance of each high inductance element is 7 nH, directivity perpendicular to the resonance direction can be realized for all signals of 5.0 GHz or more and 6 GHz or less. Further, when the same simulation was performed when the inductance of each high inductance element was larger than 7 nH, directivity perpendicular to the resonance direction could be realized for all signals having a frequency of 5.0 GHz to 6 GHz. .. From the above, when a frequency band of 5.0 GHz or more and 6 GHz or less is adopted as the first frequency band and the width Wg of the grounding portion 20 is 7 mm, the inductance of each high inductance element needs to be 7 nH or more. It turns out that there is.
　同様のシミュレーションを接地部２０の幅Ｗｇが１０ｍｍ、１２．５ｍｍ及び１５ｍｍの各場合において行った結果について、図７を用いて説明する。図７は、本実施の形態に係る接地部２０の幅Ｗｇと第２高インダクタンス部２２の各高インダクタンス要素の最小インダクタンス値Ｌｍｉｎとの関係を示すグラフである。なお、最小インダクタンス値Ｌｍｉｎは、第１周波数帯域の信号に対して、共振方向に対して概ね垂直な指向性を実現するために必要な各高インダクタンス要素のインダクタンス値を意味する。図７に示されるグラフにおいては、第１周波数帯域が５ＧＨｚ帯である場合の最小インダクタンス値Ｌｍｉｎが示されている。 The results of performing the same simulation when the width Wg of the ground contact portion 20 is 10 mm, 12.5 mm, and 15 mm will be described with reference to FIG. 7. FIG. 7 is a graph showing the relationship between the width Wg of the grounding portion 20 and the minimum inductance value Lmin of each high inductance element of the second high inductance portion 22 according to the present embodiment. The minimum inductance value Lmin means the inductance value of each high inductance element required to realize directivity substantially perpendicular to the resonance direction with respect to the signal in the first frequency band. In the graph shown in FIG. 7, the minimum inductance value Lmin when the first frequency band is the 5 GHz band is shown.
　図７に示されるように、接地部２０の幅Ｗｇが１０ｍｍ、１２．５ｍｍ及び１５ｍｍの場合、それぞれ、各高インダクタンス要素の最小インダクタンス値Ｌｍｉｎは、５ｎＨ、４ｎＨ及び２．５ｎＨとなった。このことから、接地部２０の幅Ｗｇが７ｍｍ以上である場合、各高インダクタンス要素の最小インダクタンス値Ｌｍｉｎは、７ｎＨ以上であれば十分であることが分かる。 As shown in FIG. 7, when the width Wg of the grounding portion 20 is 10 mm, 12.5 mm and 15 mm, the minimum inductance values Lmin of each high inductance element are 5 nH, 4 nH and 2.5 nH, respectively. From this, it can be seen that when the width Wg of the grounding portion 20 is 7 mm or more, the minimum inductance value Lmin of each high inductance element is 7 nH or more.
　（実施の形態２）
　実施の形態２に係るアンテナモジュールについて説明する。本実施の形態に係るアンテナモジュールは、実施の形態１に係るマルチバンドアンテナ１の適用例である。 (Embodiment 2)
The antenna module according to the second embodiment will be described. The antenna module according to the present embodiment is an application example of the multi-band antenna 1 according to the first embodiment.
　［２－１．構成］
　まず、本実施の形態に係るアンテナモジュールの構成について、図８～図１０を用いて説明する。図８及び図９は、それぞれ、本実施の形態に係るアンテナモジュール１００の構成を示す第１及び第２の平面図である。図８においては、アンテナモジュール１００の基板１４０の一方の主面１４１の平面視における平面図が示されている。また、図９においては、基板１４０上の主面１４１の裏側の主面に配置される各構成要素の平面図が示されており、基板１４０の輪郭が点線で併せて示されている。 [2-1. Constitution]
First, the configuration of the antenna module according to the present embodiment will be described with reference to FIGS. 8 to 10. 8 and 9 are first and second plan views showing the configuration of the antenna module 100 according to the present embodiment, respectively. In FIG. 8, a plan view of one main surface 141 of the substrate 140 of the antenna module 100 in a plan view is shown. Further, in FIG. 9, a plan view of each component arranged on the main surface on the back side of the main surface 141 on the substrate 140 is shown, and the outline of the substrate 140 is also shown by a dotted line.
　本実施の形態に係るアンテナモジュール１００は、アレイアンテナ１０１と、アレイアンテナ１０１を構成する各マルチバンドアンテナに信号を分配する分配器とを備えるモジュールである。本実施の形態では、アンテナモジュール１００は、無線ＬＡＮ規格に基づいて無線通信を行うモジュールであり、第１周波数帯域及び第２周波数帯域としてそれぞれ５ＧＨｚ帯及び２．４ＧＨｚ帯の信号を送受信する。図９に示されるように、アンテナモジュール１００は、分配器として３分配器１０６を備える。図８及び図９に示されるように、アンテナモジュール１００は、接地電極１９０と、線路６１、６２、６３、７１、７２及び７３と、移相器８０と、接地配線７１ｇ、７２ｇ及び７３ｇと、コネクタＣｎと、制御端子Ｔｓとをさらに備える。 The antenna module 100 according to the present embodiment is a module including an array antenna 101 and a distributor that distributes signals to each multi-band antenna constituting the array antenna 101. In the present embodiment, the antenna module 100 is a module that performs wireless communication based on the wireless LAN standard, and transmits / receives signals in the 5 GHz band and the 2.4 GHz band as the first frequency band and the second frequency band, respectively. As shown in FIG. 9, the antenna module 100 includes a 3 distributor 106 as a distributor. As shown in FIGS. 8 and 9, the antenna module 100 includes a ground electrode 190, lines 61, 62, 63, 71, 72 and 73, a phase shifter 80, and ground wiring 71 g, 72 g and 73 g. It further includes a connector Cn and a control terminal Ts.
　［２－１－１．アレイアンテナ］
　アレイアンテナ１０１は、複数のマルチバンドアンテナを有するアンテナである。本実施の形態では、アレイアンテナ１０１は、三つのマルチバンドアンテナ１ａ、１ｂ及び１ｃを有する。三つのマルチバンドアンテナ１ａ、１ｂ及び１ｃは、基板１４０を共有する。なお、基板１４０には、アンテナモジュール１００の他の構成要素も配置される。三つのマルチバンドアンテナ１ａ、１ｂ及び１ｃの各々における基板１４０以外の構成は、実施の形態１に係るマルチバンドアンテナ１と同様である。三つのマルチバンドアンテナ１ａ、１ｂ及び１ｃは、各々の共振方向（つまり、Ｙ軸方向）に垂直な方向（つまり、Ｘ軸方向）に配列されている。マルチバンドアンテナ１ａ、１ｂ及び１ｃは、実施の形態１において述べたように共振方向に垂直な指向性を有するため、マルチバンドアンテナ１ａ、１ｂ及び１ｃを共振方向に垂直な方向に配列してアレイアンテナを構成する場合に、各マルチバンドアンテナが放射する電波間の相互作用を高めることができる。 [2-1-1. Array antenna]
The array antenna 101 is an antenna having a plurality of multi-band antennas. In this embodiment, the array antenna 101 has three multi-band antennas 1a, 1b and 1c. The three multi-band antennas 1a, 1b and 1c share a substrate 140. In addition, other components of the antenna module 100 are also arranged on the substrate 140. The configurations of the three multi-band antennas 1a, 1b, and 1c other than the substrate 140 are the same as those of the multi-band antenna 1 according to the first embodiment. The three multi-band antennas 1a, 1b and 1c are arranged in a direction (that is, an X-axis direction) perpendicular to their respective resonance directions (that is, the Y-axis direction). Since the multi-band antennas 1a, 1b and 1c have directivity perpendicular to the resonance direction as described in the first embodiment, the multi-band antennas 1a, 1b and 1c are arranged in a direction perpendicular to the resonance direction and arranged in an array. When the antenna is configured, the interaction between the radio waves radiated by each multi-band antenna can be enhanced.
　基板１４０は、実施の形態１に係る基板４０と同様の構成を有する。基板１４０の一方の主面１４１に、各マルチバンドアンテナのアンテナ部１０及び接地部２０が配置される。 The substrate 140 has the same configuration as the substrate 40 according to the first embodiment. The antenna portion 10 and the ground portion 20 of each multi-band antenna are arranged on one main surface 141 of the substrate 140.
　［２－１－２．接地電極１９０］
　接地電極１９０は、グランドに接続される電極である。接地電極１９０は、基板１４０の主面１４１に配置される。本実施の形態では、接地電極１９０は、アレイアンテナ１０１の各マルチバンドアンテナの接地部２０と隣り合う位置に配置される。接地電極１９０は、基板１４０の主面１４１の裏側の主面に配置される各線路のシールド配線としても機能する。接地電極１９０は、例えば、基板１４０の主面１４１上にパターニングされた導電性部材であり、例えば、銅膜などの金属膜で形成される。接地電極１９０は、端子１９６ａ～１９６ｃ、１９７、１９８及び１９９において、基板１４０を貫通するビア配線を介して基板１４０の主面１４１の裏側の主面に配置された各導電性部材と接続される。 [2-1-2. Ground electrode 190]
The ground electrode 190 is an electrode connected to the ground. The ground electrode 190 is arranged on the main surface 141 of the substrate 140. In the present embodiment, the ground electrode 190 is arranged at a position adjacent to the ground portion 20 of each multi-band antenna of the array antenna 101. The ground electrode 190 also functions as a shield wiring for each line arranged on the main surface on the back side of the main surface 141 of the substrate 140. The ground electrode 190 is, for example, a conductive member patterned on the main surface 141 of the substrate 140, and is formed of, for example, a metal film such as a copper film. The ground electrode 190 is connected to each of the conductive members arranged on the main surface on the back side of the main surface 141 of the substrate 140 via the via wiring penetrating the substrate 140 at the terminals 196a to 196c, 197, 198 and 199. ..
　［２－１－３．３分配器］
　３分配器１０６は、第１周波数帯域及び第２周波数帯域の信号を３分配する分配器である。以下、本実施の形態に係る３分配器１０６について、図１０を用いて説明する。図１０は、本実施の形態に係る３分配器１０６の構成を示す平面図である。図１０においては、図９に示される破線枠内が拡大されて示されている。 [2-1-3.3 Distributor]
The 3-distributor 106 is a distributor that distributes signals in the first frequency band and the second frequency band into three. Hereinafter, the three distributor 106 according to the present embodiment will be described with reference to FIG. FIG. 10 is a plan view showing the configuration of the three distributor 106 according to the present embodiment. In FIG. 10, the inside of the broken line frame shown in FIG. 9 is enlarged and shown.
　図１０に示されるように、３分配器１０６は、入力端子Ｔ０と、第１出力端子Ｔ１と、第２出力端子Ｔ２と、第３出力端子Ｔ３と、第１伝送線路Ｌ１と、第２伝送線路Ｌ２と、第３伝送線路Ｌ３と、第１抵抗Ｒ１、第２抵抗Ｒ２、第３抵抗Ｒ３及び第４抵抗Ｒ４とを備える。 As shown in FIG. 10, the 3 distributor 106 includes an input terminal T0, a first output terminal T1, a second output terminal T2, a third output terminal T3, a first transmission line L1, and a second transmission. It includes a line L2, a third transmission line L3, a first resistor R1, a second resistor R2, a third resistor R3, and a fourth resistor R4.
　入力端子Ｔ０は、信号が入力される端子である。本実施の形態では、入力端子Ｔ０には、第１周波数を含む第１周波数帯域、及び、第１周波数より低い第２周波数を含む第２周波数帯域の信号が入力される。 Input terminal T0 is a terminal to which a signal is input. In the present embodiment, signals in the first frequency band including the first frequency and the second frequency band including the second frequency lower than the first frequency are input to the input terminal T0.
　第１出力端子Ｔ１、第２出力端子Ｔ２及び第３出力端子Ｔ３は、それぞれ、入力端子Ｔ０から入力された信号が３分配された三つの分配信号を出力する端子である。本実施の形態では、同位相の三つの分配信号が、それぞれ、第１出力端子Ｔ１、第２出力端子Ｔ２及び第３出力端子Ｔ３から出力される。 The first output terminal T1, the second output terminal T2, and the third output terminal T3 are terminals that output three distributed signals in which the signal input from the input terminal T0 is divided into three, respectively. In the present embodiment, the three distributed signals having the same phase are output from the first output terminal T1, the second output terminal T2, and the third output terminal T3, respectively.
　第１伝送線路Ｌ１、第２伝送線路Ｌ２及び第３伝送線路Ｌ３は、入力端子Ｔ０と第１出力端子Ｔ１、第２出力端子Ｔ２及び第３出力端子Ｔ３との間をそれぞれ接続する線路である。 The first transmission line L1, the second transmission line L2, and the third transmission line L3 are lines connecting the input terminal T0 and the first output terminal T1, the second output terminal T2, and the third output terminal T3, respectively. ..
　第１伝送線路Ｌ１は、入力端子Ｔ０側から順に、第１接続点ＣＰ１で直列に接続された第１入力側線路Ｌ１１及び第１出力側線路Ｌ１２を含む。第２伝送線路Ｌ２は、入力端子Ｔ０側から順に、第２接続点ＣＰ２で直列に接続された第２入力側線路Ｌ２１及び第２出力側線路Ｌ２２を含む。第３伝送線路Ｌ３は、入力端子Ｔ０側から順に、第３接続点ＣＰ３で直列に接続された第３入力側線路Ｌ３１及び第３出力側線路Ｌ３２を含む。 The first transmission line L1 includes a first input side line L11 and a first output side line L12 connected in series at the first connection point CP1 in order from the input terminal T0 side. The second transmission line L2 includes a second input side line L21 and a second output side line L22 connected in series at the second connection point CP2 in order from the input terminal T0 side. The third transmission line L3 includes a third input side line L31 and a third output side line L32 connected in series at the third connection point CP3 in order from the input terminal T0 side.
　図１０に示されるように、第２入力側線路Ｌ２１の幅は、第１入力側線路Ｌ１１及び第３入力側線路Ｌ３１の幅より狭い。このように、第２入力側線路Ｌ２１の幅を狭くすることにより、第２入力側線路Ｌ２１を湾曲させることで電気長を確保しつつ、第１入力側線路Ｌ１１及び第３入力側線路Ｌ３１で挟まれた領域内に第２入力側線路Ｌ２１を収めることが容易となる。 As shown in FIG. 10, the width of the second input side line L21 is narrower than the width of the first input side line L11 and the third input side line L31. In this way, by narrowing the width of the second input side line L21, the second input side line L21 is curved to secure the electric length, and the first input side line L11 and the third input side line L31 It becomes easy to fit the second input side line L21 in the sandwiched area.
　また、第２出力側線路Ｌ２２の幅は、第１出力側線路Ｌ１２及び第３出力側線路Ｌ３２の幅より狭い。このように、第２出力側線路Ｌ２２の幅を狭くすることにより、第２出力側線路Ｌ２２を湾曲させることで電気長を確保しつつ、第１出力側線路Ｌ１２及び第３出力側線路Ｌ３２で挟まれた領域内に第２出力側線路Ｌ２２を収めることが容易となる。 Further, the width of the second output side line L22 is narrower than the width of the first output side line L12 and the third output side line L32. In this way, by narrowing the width of the second output side line L22, the second output side line L22 is curved to secure the electric length, and the first output side line L12 and the third output side line L32 It becomes easy to fit the second output side line L22 in the sandwiched region.
　第１入力側線路Ｌ１１、第２入力側線路Ｌ２１及び第３入力側線路Ｌ３１の各々の電気長は、第１周波数の１／４波長である。第１伝送線路Ｌ１、第２伝送線路Ｌ２及び第３伝送線路Ｌ３の各々の電気長は、第１周波数より低い第２周波数の１／４波長である。 The electrical length of each of the first input side line L11, the second input side line L21, and the third input side line L31 is 1/4 wavelength of the first frequency. The electrical length of each of the first transmission line L1, the second transmission line L2, and the third transmission line L3 is 1/4 wavelength of the second frequency lower than the first frequency.
　第１接続点ＣＰ１と第２接続点ＣＰ２との間、第３接続点ＣＰ３と第２接続点ＣＰ２との間、第１出力端子Ｔ１と第２出力端子Ｔ２との間、及び、第３出力端子Ｔ３と第２出力端子Ｔ２との間は、それぞれ、第１抵抗Ｒ１、第２抵抗Ｒ２、第３抵抗Ｒ３及び第４抵抗Ｒ４を介して接続される。第１抵抗Ｒ１、第２抵抗Ｒ２、第３抵抗Ｒ３及び第４抵抗Ｒ４は、吸収抵抗である。例えば、３分配器１０６の出力側のインピーダンスが５０Ωである場合、第３抵抗Ｒ３及び第４抵抗Ｒ４の抵抗値は、出力側のインピーダンスの２倍の１００Ωであり、第１抵抗Ｒ１及び第２抵抗Ｒ２の抵抗値は、出力側のインピーダンスの２倍以上４倍以下、つまり、１００Ω以上２００Ω以下である。本実施の形態では、また、第１抵抗Ｒ１、第２抵抗Ｒ２、第３抵抗Ｒ３及び第４抵抗Ｒ４の抵抗値は同一であり、いずれも１００Ωである。 Between the first connection point CP1 and the second connection point CP2, between the third connection point CP3 and the second connection point CP2, between the first output terminal T1 and the second output terminal T2, and the third output. The terminal T3 and the second output terminal T2 are connected via a first resistor R1, a second resistor R2, a third resistor R3, and a fourth resistor R4, respectively. The first resistor R1, the second resistor R2, the third resistor R3, and the fourth resistor R4 are absorption resistors. For example, when the impedance on the output side of the 3 distributor 106 is 50Ω, the resistance values of the 3rd resistor R3 and the 4th resistor R4 are 100Ω, which is twice the impedance on the output side, and the 1st resistor R1 and the 2nd resistor are The resistance value of the resistor R2 is twice or more and four times or less the impedance on the output side, that is, 100Ω or more and 200Ω or less. In the present embodiment, the resistance values of the first resistor R1, the second resistor R2, the third resistor R3, and the fourth resistor R4 are the same, and all of them are 100Ω.
　本実施の形態に係る３分配器１０６は、以上のような構成を備えることにより、一般的なウィルキンソン型の分配器より小型化できるという効果が奏される。例えば、ウィルキンソン型の分配器では、本実施の形態に係る３分配器１０６の第１出力側線路Ｌ１２、第２出力側線路Ｌ２２及び第３出力側線路Ｌ３２に対応する線路の電気長を、第２周波数の１／４波長とする必要がある。これに対して、本実施の形態に係る３分配器１０６では、第１接続点ＣＰ１と第２接続点ＣＰ２の間、及び、第３接続点ＣＰ３と第２接続点ＣＰ２の間に吸収抵抗を接続することで、第１伝送線路Ｌ１、第２伝送線路Ｌ２及び第３伝送線路Ｌ３の電気長を第２周波数の１／４波長とすることができる。したがって、本実施の形態に係る３分配器１０６では、第１伝送線路Ｌ１、第２伝送線路Ｌ２及び第３伝送線路Ｌ３の電気長を、第１周波数の１／４波長だけ、ウィルキンソン型の分配器より小型化できる。これにより、アンテナモジュール１００を小型化できる。 The three distributor 106 according to the present embodiment has the effect of being smaller than a general Wilkinson type distributor by having the above configuration. For example, in the Wilkinson type distributor, the electrical lengths of the lines corresponding to the first output side line L12, the second output side line L22, and the third output side line L32 of the three distributor 106 according to the present embodiment are set to the second. It needs to be 1/4 wavelength of 2 frequencies. On the other hand, in the 3 distributor 106 according to the present embodiment, an absorption resistor is provided between the first connection point CP1 and the second connection point CP2 and between the third connection point CP3 and the second connection point CP2. By connecting, the electrical length of the first transmission line L1, the second transmission line L2, and the third transmission line L3 can be set to 1/4 wavelength of the second frequency. Therefore, in the three-distributor 106 according to the present embodiment, the electrical lengths of the first transmission line L1, the second transmission line L2, and the third transmission line L3 are distributed by the Wilkinson type by only 1/4 wavelength of the first frequency. It can be made smaller than a vessel. As a result, the antenna module 100 can be miniaturized.
　［２－１－４．コネクタ］
　コネクタＣｎは、外部からアンテナモジュール１００に信号を入力するための接続部材である。コネクタＣｎの構成は特に限定されないが、本実施の形態では、同軸コネクタである。コネクタＣｎの信号配線は、３分配器１０６の入力端子Ｔ０に接続される。これにより、コネクタＣｎを介して外部から３分配器１０６に信号を入力できる。コネクタＣｎは、グランドに接続されるコネクタグランドＣｇを有する。コネクタＣｎのシールド配線は、にコネクタグランドＣｇに接続される。コネクタグランドＣｇは、基板１４０を貫通するビア配線を介して接地電極１９０の端子１９８に接続される。 [2-1-4. connector]
The connector Cn is a connecting member for inputting a signal to the antenna module 100 from the outside. The configuration of the connector Cn is not particularly limited, but in the present embodiment, it is a coaxial connector. The signal wiring of the connector Cn is connected to the input terminal T0 of the 3 distributor 106. As a result, a signal can be input to the 3 distributor 106 from the outside via the connector Cn. The connector Cn has a connector ground Cg connected to the ground. The shield wiring of the connector Cn is connected to the connector ground Cg. The connector ground Cg is connected to the terminal 198 of the ground electrode 190 via the via wiring penetrating the substrate 140.
　［２－１－５．線路６１～６３］
　線路６１は、線路７１と３分配器１０６の第１出力端子Ｔ１とを接続する導電性部材である。線路６１の電気長は、線路７１～７３に分配される分配信号の間に与える位相差と、線路６２及び６３の電気長とに基づいて設定される。なお、線路６１には、移相器８０が接続されており、移相器８０の状態に応じて線路６１における位相の遅延量が変化する。 [2-1-5. Railroad tracks 61-63]
The line 61 is a conductive member that connects the line 71 and the first output terminal T1 of the 3 distributor 106. The electric length of the line 61 is set based on the phase difference given between the distributed signals distributed to the lines 71 to 73 and the electric lengths of the lines 62 and 63. A phase shifter 80 is connected to the line 61, and the amount of phase delay in the line 61 changes according to the state of the phase shifter 80.
　線路６２は、線路７２と３分配器１０６の第２出力端子Ｔ２とを接続する導電性部材である。線路６２の電気長は、線路７１～７３に分配される分配信号の間に与える位相差と、線路６１及び６３の電気長とに基づいて設定される。 The line 62 is a conductive member that connects the line 72 and the second output terminal T2 of the 3 distributor 106. The electric length of the line 62 is set based on the phase difference given between the distributed signals distributed to the lines 71 to 73 and the electric length of the lines 61 and 63.
　線路６３は、線路７３と３分配器１０６の第３出力端子Ｔ３とを接続する導電性部材である。線路６３の電気長は、線路７１～７３に分配される分配信号の間に与える位相差と、線路６１及び６２の電気長とに基づいて設定される。 The line 63 is a conductive member that connects the line 73 and the third output terminal T3 of the 3 distributor 106. The electric length of the line 63 is set based on the phase difference given between the distributed signals distributed to the lines 71 to 73 and the electric lengths of the lines 61 and 62.
　［２－１－６．移相器］
　移相器８０は、線路６１に接続され、線路６１における分配信号の位相の遅延量を変化させる機器である。移相器８０は、ロードライン（loaded line）型移相器である。移相器８０は、線路８１及び８２と、コンデンサ８３及び８４と、ＰＩＮダイオード８６及び８７と、接地電極８５とを有する。 [2-1-6. Phaser]
The phase shifter 80 is a device connected to the line 61 and changing the amount of phase delay of the distributed signal on the line 61. The phase shifter 80 is a loaded line type phase shifter. The phase shifter 80 has lines 81 and 82, capacitors 83 and 84, PIN diodes 86 and 87, and a ground electrode 85.
　線路８１は、線路６１にコンデンサ８３を介して結合される線路である。線路８１の一端は、コンデンサ８３に接続され、他端は、ＰＩＮダイオード８６に接続される。 The line 81 is a line coupled to the line 61 via a capacitor 83. One end of the line 81 is connected to the capacitor 83 and the other end is connected to the PIN diode 86.
　線路８２は、線路６１にコンデンサ８４を介して結合される線路である。線路８２は、線路８１が結合される位置とは異なる位置において、線路６１に結合される。線路８２の一端は、コンデンサ８４に接続され、他端は、ＰＩＮダイオード８７に接続される。 The line 82 is a line coupled to the line 61 via a capacitor 84. The line 82 is coupled to the line 61 at a position different from the position where the line 81 is connected. One end of the line 82 is connected to the capacitor 84 and the other end is connected to the PIN diode 87.
　コンデンサ８３及び８４は、それぞれ、線路６１と線路８１及び８２とを結合するための素子である。言い換えると、移相器８０と線路６１とは、コンデンサ８３及び８４によって結合される。線路８１及び８２が、それぞれ、コンデンサ８３及び８４を介して線路６１に結合されることで、線路８１及び８２と線路６１との間に直流電流が流れることを抑制できる。 The capacitors 83 and 84 are elements for connecting the line 61 and the lines 81 and 82, respectively. In other words, the phase shifter 80 and the line 61 are coupled by capacitors 83 and 84. By coupling the lines 81 and 82 to the line 61 via the capacitors 83 and 84, respectively, it is possible to suppress the flow of direct current between the lines 81 and 82 and the line 61.
　接地電極８５は、グランドに接続される電極である。本実施の形態では、基板１４０を貫通するビア配線を介して接地電極１９０の端子１９７に接続される。 The ground electrode 85 is an electrode connected to the ground. In the present embodiment, the ground electrode 190 is connected to the terminal 197 via a via wiring penetrating the substrate 140.
　ＰＩＮダイオード８６及び８７は、それぞれ、線路８１及び８２と接地電極８５との間の接続状態を開状態又は閉状態に切り替えるスイッチである。ＰＩＮダイオード８６及び８７は、制御端子Ｔｓに入力される制御信号によって制御される。移相器８０において、ＰＩＮダイオード８６及び８７の状態を共に開状態、又は、共に閉状態とすることで、線路６１における分配信号の位相の遅延量を切り替えられる。 The PIN diodes 86 and 87 are switches that switch the connection state between the lines 81 and 82 and the ground electrode 85, respectively, between the open state and the closed state. The PIN diodes 86 and 87 are controlled by a control signal input to the control terminals Ts. In the phase shifter 80, the phase delay amount of the distributed signal on the line 61 can be switched by setting the states of the PIN diodes 86 and 87 in the open state or the closed state together.
　［２－１－７．制御端子］
　制御端子Ｔｓは、移相器８０のＰＩＮダイオード８６及び８７の状態を制御するための制御信号が入力される端子である。制御端子Ｔｓは、接地端子を有し、当該接地端子は、基板１４０上の端子１９１、及び、基板１４０を貫通するビア配線を介して接地電極１９０の端子１９９に接続される。 [2-1-7. Control terminal]
The control terminal Ts is a terminal to which a control signal for controlling the states of the PIN diodes 86 and 87 of the phase shifter 80 is input. The control terminal Ts has a ground terminal, and the ground terminal is connected to the terminal 191 on the substrate 140 and the terminal 199 of the ground electrode 190 via the via wiring penetrating the substrate 140.
　［２－１－８．線路７１～７３］
　線路７１、７２及び７３の各々は、３分配器１０６によって分配された分配信号が入力される長尺状の導電性部材であり、図９のＹ軸方向（つまり、各マルチバンドアンテナの共振方向）に延びる。 [2-1-8. Railroad tracks 71-73]
Each of the lines 71, 72, and 73 is a long conductive member to which the distribution signal distributed by the three distributor 106 is input, and is in the Y-axis direction of FIG. 9 (that is, the resonance direction of each multi-band antenna). ).
　本実施の形態では、線路７１の一方の端部は、線路６１に接続される。線路７１の他方の端部には、端子７４が配置されている。端子７４は、基板１４０を貫通するビア配線を介してマルチバンドアンテナ１ａの入力端子１６に接続される。これにより、線路７１は、線路６１を介して３分配器１０６の第１出力端子Ｔ１から分配信号が入力され、マルチバンドアンテナ１ａに分配信号を出力する。 In the present embodiment, one end of the line 71 is connected to the line 61. A terminal 74 is arranged at the other end of the line 71. The terminal 74 is connected to the input terminal 16 of the multi-band antenna 1a via a via wiring penetrating the substrate 140. As a result, the line 71 receives the distribution signal from the first output terminal T1 of the 3 distributor 106 via the line 61, and outputs the distribution signal to the multi-band antenna 1a.
　線路７２の一方の端部は、線路６２に接続される。線路７２の他方の端部には、端子７６が配置されている。端子７６は、基板１４０を貫通するビア配線を介してマルチバンドアンテナ１ｂの入力端子１６に接続される。これにより、線路７２は、線路６２を介して３分配器１０６の第２出力端子Ｔ２から分配信号が入力され、マルチバンドアンテナ１ｂに分配信号を出力する。 One end of the line 72 is connected to the line 62. A terminal 76 is arranged at the other end of the line 72. The terminal 76 is connected to the input terminal 16 of the multi-band antenna 1b via a via wiring penetrating the substrate 140. As a result, the line 72 receives the distribution signal from the second output terminal T2 of the 3 distributor 106 via the line 62, and outputs the distribution signal to the multi-band antenna 1b.
　線路７３の一方の端部は、線路６３に接続される。線路７３の他方の端部には、端子７８が配置されている。端子７８は、基板１４０を貫通するビア配線を介してマルチバンドアンテナ１ｃの入力端子１６に接続される。これにより、線路７３は、線路６３を介して３分配器１０６の第３出力端子Ｔ３から分配信号が入力され、マルチバンドアンテナ１ｃに分配信号を出力する。 One end of the line 73 is connected to the line 63. A terminal 78 is arranged at the other end of the line 73. The terminal 78 is connected to the input terminal 16 of the multi-band antenna 1c via a via wiring penetrating the substrate 140. As a result, the line 73 receives the distribution signal from the third output terminal T3 of the 3 distributor 106 via the line 63, and outputs the distribution signal to the multi-band antenna 1c.
　［２－１－９．接地配線７１ｇ～７３ｇ］
　二つの接地配線７１ｇの各々は、グランドに接続され、線路７１に沿って配置される長尺状の導電性部材であり、図９のＹ軸方向に延びる。二つの接地配線７１ｇは、図９のＸ軸方向に配列され、二つの接地配線７１ｇの間に線路７１が配置される。二つの接地配線７１ｇ及び線路７１は、互いに離隔して配置される。二つの接地配線７１ｇの各々の一方の端部には、端子７５ｇが配置され、他方の端部には、端子７４ｇが配置される。端子７５ｇは、基板１４０を貫通するビア配線を介して接地電極１９０の端子１９６ａに接続される。端子７４ｇは、基板１４０を貫通するビア配線を介してマルチバンドアンテナ１ａの接地部２０の接地端子２６に接続される。 [2-1-9. Ground wiring 71g-73g]
Each of the two ground wires 71g is a long conductive member connected to the ground and arranged along the line 71, and extends in the Y-axis direction of FIG. The two ground wires 71 g are arranged in the X-axis direction of FIG. 9, and the line 71 is arranged between the two ground wires 71 g. The two ground wires 71g and the line 71 are arranged apart from each other. A terminal 75g is arranged at one end of each of the two ground wires 71g, and a terminal 74g is arranged at the other end. The terminal 75g is connected to the terminal 196a of the ground electrode 190 via a via wiring penetrating the substrate 140. The terminal 74g is connected to the ground terminal 26 of the ground portion 20 of the multi-band antenna 1a via a via wiring penetrating the substrate 140.
　二つの接地配線７２ｇの各々は、グランドに接続され、線路７２に沿って配置される長尺状の導電性部材であり、図９のＹ軸方向に延びる。二つの接地配線７２ｇは、図９のＸ軸方向に配列され、二つの接地配線７２ｇの間に線路７２が配置される。二つの接地配線７２ｇ及び線路７２は、互いに離隔して配置される。二つの接地配線７２ｇの各々の一方の端部には、端子７７ｇが配置され、他方の端部には、端子７６ｇが配置される。端子７７ｇは、基板１４０を貫通するビア配線を介して接地電極１９０の端子１９６ｂに接続される。端子７６ｇは、基板１４０を貫通するビア配線を介してマルチバンドアンテナ１ｂの接地部２０の接地端子２６に接続される。 Each of the two grounding wires 72g is a long conductive member connected to the ground and arranged along the line 72, and extends in the Y-axis direction of FIG. The two ground wires 72 g are arranged in the X-axis direction of FIG. 9, and the line 72 is arranged between the two ground wires 72 g. The two ground wires 72 g and the line 72 are arranged apart from each other. A terminal 77g is arranged at one end of each of the two ground wires 72g, and a terminal 76g is arranged at the other end. The terminal 77g is connected to the terminal 196b of the ground electrode 190 via the via wiring penetrating the substrate 140. The terminal 76g is connected to the ground terminal 26 of the ground portion 20 of the multi-band antenna 1b via a via wiring penetrating the substrate 140.
　二つの接地配線７３ｇの各々は、グランドに接続され、線路７３に沿って配置される長尺状の導電性部材であり、図９のＹ軸方向に延びる。二つの接地配線７３ｇは、図９のＸ軸方向に配列され、二つの接地配線７３ｇの間に線路７３が配置される。二つの接地配線７３ｇ及び線路７３は、互いに離隔して配置される。二つの接地配線７３ｇの各々の一方の端部には、端子７９ｇが配置され、他方の端部には、端子７８ｇが配置される。端子７９ｇは、基板１４０を貫通するビア配線を介して接地電極１９０の端子１９６ｃに接続される。端子７８ｇは、基板１４０を貫通するビア配線を介してマルチバンドアンテナ１ｃの接地部２０の接地端子２６に接続される。 Each of the two ground wires 73g is a long conductive member connected to the ground and arranged along the line 73, and extends in the Y-axis direction of FIG. The two ground wires 73g are arranged in the X-axis direction of FIG. 9, and the line 73 is arranged between the two ground wires 73g. The two ground wires 73g and the line 73 are arranged apart from each other. A terminal 79g is arranged at one end of each of the two ground wires 73g, and a terminal 78g is arranged at the other end. The terminal 79g is connected to the terminal 196c of the ground electrode 190 via the via wiring penetrating the substrate 140. The terminal 78g is connected to the ground terminal 26 of the ground portion 20 of the multi-band antenna 1c via a via wiring penetrating the substrate 140.
　本実施の形態に係る３分配器１０６の各伝送線路、線路６１、６２、６３、７１～７３、８１及び８２、並びに、接地配線７１ｇ、７２ｇ及び７３ｇは、例えば、基板１４０の主面１４１の裏側の主面上にパターニングされた導電性部材であり、例えば、銅膜などの金属膜で形成される。 The transmission lines, lines 61, 62, 63, 71 to 73, 81 and 82 of the three distributor 106 according to the present embodiment, and the ground wirings 71g, 72g and 73g are, for example, the main surface 141 of the substrate 140. It is a conductive member patterned on the main surface on the back side, and is formed of, for example, a metal film such as a copper film.
　線路７１、７２及び７３は、それぞれ、接地配線７１ｇ、７２ｇ及び７３ｇとともにコプレーナ線路を形成する。 The lines 71, 72 and 73 form a coplanar line together with the ground wires 71 g, 72 g and 73 g, respectively.
　本実施の形態に係る３分配器１０６の各伝送線路、線路６１、６２及び６３、移相器８０の線路８１及び８２の各線路は、基板１４０を介して接地電極１９０に対向する位置に配置されている。これにより、各線路と接地電極１９０とがマイクロストリップ線路を形成する。 The transmission lines of the three distributor 106 and the lines 61, 62 and 63 of the phase shifter 80 and the lines 81 and 82 of the phase shifter 80 according to the present embodiment are arranged at positions facing the ground electrode 190 via the substrate 140. Has been done. As a result, each line and the ground electrode 190 form a microstrip line.
　図９に示される線路７１及び接地配線７１ｇは、図８に示されるマルチバンドアンテナ１ａの接地部２０に対向する位置に配置される。接地部２０の幅（Ｘ軸方向の寸法）は、二つの接地配線７１ｇのうち、線路７１に沿って配置される部分（つまり、図９に示される例では、接地配線７１ｇのうち、端子７５ｇの周辺を除く部分）のＸ軸方向における外側の端縁間の距離より大きい。つまり、接地部２０は、Ｘ軸方向において、二つの接地配線７１ｇより外側に突出している。本実施の形態では、接地部２０の幅は７ｍｍであり、二つの接地配線７１ｇのうち、線路７１に沿って配置される部分のＸ軸方向における外側の端縁間の距離は、３ｍｍである。これにより、接地部２０のＸ軸方向の端部に流れる電流（図１の破線矢印参照）に起因する電波が二つの接地配線７１ｇによって遮蔽されることを抑制できる。したがって、マルチバンドアンテナ１ａのＺ軸方向における指向性の劣化を抑制できる。マルチバンドアンテナ１ｂ及び１ｃの接地部２０の幅も、マルチバンドアンテナ１ａの接地部２０の幅と同様に、対向する二つの接地配線のうち、線路７２及び７３に沿って配置される部分のＸ軸方向における外側の端縁間の距離より大きい。 The line 71 and the ground wiring 71g shown in FIG. 9 are arranged at positions facing the ground portion 20 of the multi-band antenna 1a shown in FIG. The width (dimension in the X-axis direction) of the grounding portion 20 is the portion of the two grounding wires 71g that is arranged along the line 71 (that is, in the example shown in FIG. 9, the terminal 75g of the grounding wiring 71g. It is larger than the distance between the outer edges in the X-axis direction (the portion excluding the periphery of). That is, the grounding portion 20 projects outward from the two grounding wires 71g in the X-axis direction. In the present embodiment, the width of the grounding portion 20 is 7 mm, and the distance between the outer edges of the two grounding wires 71g arranged along the line 71 in the X-axis direction is 3 mm. .. As a result, it is possible to prevent the radio waves caused by the current flowing through the end of the grounding portion 20 in the X-axis direction (see the broken arrow in FIG. 1) from being shielded by the two grounding wires 71g. Therefore, deterioration of the directivity of the multi-band antenna 1a in the Z-axis direction can be suppressed. The width of the grounding portion 20 of the multi-band antennas 1b and 1c is also the same as the width of the grounding portion 20 of the multi-band antenna 1a, which is the X of the portion of the two opposing grounding wires arranged along the lines 72 and 73. Greater than the distance between the outer edges in the axial direction.
　［２－２．作用及び効果］
　次に、本実施の形態に係るアンテナモジュール１００の作用及び効果について説明する。上述したように、本実施の形態に係るアンテナモジュール１００においては、線路６１、６２及び６３の電気長を適切に設定することで、アレイアンテナ１０１を構成する各マルチバンドアンテナに入力される信号の位相を調整することができる。これにより、アレイアンテナ１０１の指向性を調整することができる。例えば、アンテナモジュール１００の近くにアンテナモジュール１００が扱う周波数帯域と近い周波数帯域の信号を送受信するアンテナが存在する場合には、アンテナモジュール１００のアレイアンテナ１０１から当該他のアンテナへ向かう向きにおけるアレイアンテナ１０１の指向性を低減することで、アンテナモジュール１００と当該他のアンテナとの間の電波の干渉を低減できる。このようなアレイアンテナ１０１の指向性について、図１１を用いて説明する。図１１は、本実施の形態に係るアレイアンテナ１０１の指向性を示すグラフである。なお、図１１には、アンテナモジュール１００の移相器８０のＰＩＮダイオード８６及び８７をいずれもＯＦＦにした場合の指向性が示されている。なお、図１１における角度θｚｘは、各図中のＺ軸方向からＸ軸方向に向かって傾斜する角度を示す。 [2-2. Action and effect]
Next, the operation and effect of the antenna module 100 according to the present embodiment will be described. As described above, in the antenna module 100 according to the present embodiment, by appropriately setting the electric lengths of the lines 61, 62, and 63, the signal input to each multi-band antenna constituting the array antenna 101 can be obtained. The phase can be adjusted. Thereby, the directivity of the array antenna 101 can be adjusted. For example, when there is an antenna near the antenna module 100 that transmits / receives signals in a frequency band close to the frequency band handled by the antenna module 100, the array antenna in the direction from the array antenna 101 of the antenna module 100 toward the other antenna. By reducing the directivity of 101, it is possible to reduce the interference of radio waves between the antenna module 100 and the other antenna. The directivity of such an array antenna 101 will be described with reference to FIG. FIG. 11 is a graph showing the directivity of the array antenna 101 according to the present embodiment. Note that FIG. 11 shows the directivity when both the PIN diodes 86 and 87 of the phase shifter 80 of the antenna module 100 are turned off. The angle θzx in FIG. 11 indicates an angle that is inclined from the Z-axis direction to the X-axis direction in each figure.
　図１１に示される例では、Ｘ軸方向の正側の方向における指向性が低減されている。このため、このような指向性を有するアレイアンテナ１０１のＸ軸方向の正側に他のアンテナがある場合に、アレイアンテナ１０１と当該他のアンテナとの干渉を低減できる。 In the example shown in FIG. 11, the directivity in the positive direction in the X-axis direction is reduced. Therefore, when there is another antenna on the positive side of the array antenna 101 having such directivity in the X-axis direction, the interference between the array antenna 101 and the other antenna can be reduced.
　また、本実施の形態に係るアンテナモジュール１００においては、移相器８０によって、マルチバンドアンテナ１ａに入力する信号の位相を切り替えることができる。本実施の形態に係る移相器８０によっては、ＰＩＮダイオード８６及びｂ８７をいずれもＯＦＦとする場合と、いずれもＯＮとする場合とで、マルチバンドアンテナ１ａに入力される信号の位相を約５０°変化させることができる。ここで、移相器８０による効果について、図１２を用いて説明する。 Further, in the antenna module 100 according to the present embodiment, the phase shifter 80 can switch the phase of the signal input to the multi-band antenna 1a. Depending on the phase shifter 80 according to the present embodiment, the phase of the signal input to the multi-band antenna 1a is about 50 depending on whether the PIN diodes 86 and b87 are both OFF and both are ON. ° Can be changed. Here, the effect of the phase shifter 80 will be described with reference to FIG.
　図１２は、本実施の形態に係るアレイアンテナ１０１の移相器８０の状態を変化させた場合の指向性を示すグラフである。図１２には、移相器８０のＰＩＮダイオード８６及び８７をいずれもＯＮにした場合の指向性が示されている。なお、図１２における角度θｚｘは、各図中のＺ軸方向からＸ軸方向に向かって傾斜する角度を示す。図１１及び図１２に示される各指向性からわかるように、移相器８０によってアレイアンテナ１０１の指向性を大きく変化させることができる。このような移相器８０の効果は、アンテナモジュール１００の周辺における電波環境が変化する場合に有効である。例えば、アンテナモジュール１００及び他のアンテナの配置を変更した場合には、アンテナモジュール１００と他のアンテナとの相対位置が変わり得る。また、アンテナモジュール１００と他のアンテナとの相対位置が変化しないとしても、アンテナモジュール１００及び他のアンテナを移動させる場合には、周辺の構造物とアンテナモジュール１００との相対位置が変化し得る。この場合、周辺の構造物によって、他のアンテナから放射された電波が反射されるため、アンテナモジュール１００のアレイアンテナ１０１において、当該反射された電波の干渉が問題となり得る。このように電波環境が変化する場合に、移相器８０を用いてアレイアンテナ１０１の指向性を変化させることで、他の電波との干渉を抑制し得る。 FIG. 12 is a graph showing the directivity when the state of the phase shifter 80 of the array antenna 101 according to the present embodiment is changed. FIG. 12 shows the directivity when both the PIN diodes 86 and 87 of the phase shifter 80 are turned on. The angle θzx in FIG. 12 indicates an angle inclined from the Z-axis direction to the X-axis direction in each figure. As can be seen from the directivity shown in FIGS. 11 and 12, the directivity of the array antenna 101 can be significantly changed by the phase shifter 80. The effect of the phase shifter 80 is effective when the radio wave environment around the antenna module 100 changes. For example, when the arrangement of the antenna module 100 and other antennas is changed, the relative positions of the antenna module 100 and the other antennas may change. Further, even if the relative positions of the antenna module 100 and the other antennas do not change, when the antenna module 100 and the other antennas are moved, the relative positions of the surrounding structures and the antenna module 100 may change. In this case, since the radio waves radiated from other antennas are reflected by the surrounding structures, the interference of the reflected radio waves may become a problem in the array antenna 101 of the antenna module 100. When the radio wave environment changes in this way, interference with other radio waves can be suppressed by changing the directivity of the array antenna 101 using the phase shifter 80.
　［２－３．適用例］
　次に、本実施の形態に係るアンテナモジュール１００の適用例について図１３を用いて説明する。図１３は、本実施の形態に係るアンテナモジュール１００を備える音響装置１０３の構成を示す斜視図である。 [2-3. Application example]
Next, an application example of the antenna module 100 according to the present embodiment will be described with reference to FIG. FIG. 13 is a perspective view showing the configuration of an audio device 103 including the antenna module 100 according to the present embodiment.
　図１３に示される音響装置１０３は、主に、筐体１０３ｃと、アンテナモジュール１００、１００ａ及び１０４と、スピーカＳｐ０～Ｓｐ４とを備える。なお、図１３においては、各構成要素の配置を示すために、筐体１０３ｃは輪郭のみが点線で示されている。 The audio device 103 shown in FIG. 13 mainly includes a housing 103c, antenna modules 100, 100a and 104, and speakers Sp0 to Sp4. In FIG. 13, only the outline of the housing 103c is shown by a dotted line in order to show the arrangement of each component.
　アンテナモジュール１００ａは、アンテナモジュール１００と同様に無線ＬＡＮ規格に基づいて無線通信を行うモジュールであり、５ＧＨｚ帯及び２．４ＧＨｚ帯の信号を送受信する。アンテナモジュール１００ａは、アンテナモジュール１００と同様のモジュールであり、各構成要素の構造及び配置が、アンテナモジュール１００に対して左右反転されている。これに伴い、アンテナモジュール１００ａが備えるアレイアンテナの指向性は、アンテナモジュール１００のアレイアンテナ１０１の指向性を左右反転させたもの（つまり、図１１及び図１２に示されるグラフを左右反転させたもの）となる。 The antenna module 100a is a module that performs wireless communication based on the wireless LAN standard like the antenna module 100, and transmits / receives signals in the 5 GHz band and the 2.4 GHz band. The antenna module 100a is a module similar to the antenna module 100, and the structure and arrangement of each component are reversed left and right with respect to the antenna module 100. Along with this, the directivity of the array antenna included in the antenna module 100a is the one in which the directivity of the array antenna 101 of the antenna module 100 is inverted left and right (that is, the graphs shown in FIGS. 11 and 12 are inverted left and right). ).
　アンテナモジュール１０４は、他の機器との間で無線通信を行うモジュールである。本実施の形態では、無線ＬＡＮ規格とは異なる規格に基づいて、２．４ＧＨｚ帯の信号を他の音響機器に送信するモジュールである。ここで他の音響機器は、例えば、サブウーハなどである。 The antenna module 104 is a module that performs wireless communication with other devices. In the present embodiment, it is a module that transmits a 2.4 GHz band signal to another audio device based on a standard different from the wireless LAN standard. Here, other audio equipment is, for example, a subwoofer.
　音響装置１０３は、上述したように、２．４ＧＨｚ帯の信号を扱う三つのアンテナモジュール１００、１００ａ及び１０４を備えるため、これらのモジュール間で電波の干渉が発生し得る。しかしながら、本実施の形態に係るアンテナモジュール１００のアレイアンテナ１０１は、図１１に示されるようにＸ軸方向正側において指向性が低いため、他のモジュールとの間における電波の干渉を低減できる。 As described above, since the sound device 103 includes three antenna modules 100, 100a and 104 that handle signals in the 2.4 GHz band, radio wave interference may occur between these modules. However, since the array antenna 101 of the antenna module 100 according to the present embodiment has low directivity on the positive side in the X-axis direction as shown in FIG. 11, it is possible to reduce radio wave interference with other modules.
　また、アンテナモジュール１００ａは、アンテナモジュール１００を左右反転した構造を有するため、アンテナモジュール１００ａのアレイアンテナは、Ｘ軸方向負側において指向性が低い。したがって、アンテナモジュール１００ａのＸ軸方向負側に配置された他のアンテナモジュールとの間における電波の干渉を低減できる。 Further, since the antenna module 100a has a structure in which the antenna module 100 is flipped horizontally, the array antenna of the antenna module 100a has low directivity on the negative side in the X-axis direction. Therefore, it is possible to reduce the interference of radio waves with other antenna modules arranged on the negative side in the X-axis direction of the antenna module 100a.
　また、音響装置１０３と、その周辺の構造物との位置関係によっては、アンテナモジュール１０４から放射された電波が構造物によって反射されて、アンテナモジュール１００及び１００ａに到達し得る。このような状況で、アンテナモジュール１００及び１００ａにおいて、当該反射された電波との干渉が問題となる場合には、アンテナモジュール１００及び１００ａの各移相器の設定を変えて各アレイアンテナの指向性を変化させることで、当該反射された電波との干渉を低減し得る。 Further, depending on the positional relationship between the acoustic device 103 and the surrounding structure, the radio wave radiated from the antenna module 104 may be reflected by the structure and reach the antenna modules 100 and 100a. In such a situation, if interference with the reflected radio wave becomes a problem in the antenna modules 100 and 100a, the directivity of each array antenna is changed by changing the setting of each phase shifter of the antenna modules 100 and 100a. By changing, the interference with the reflected radio wave can be reduced.
　（実施の形態３）
　実施の形態３に係るマルチバンドアンテナについて説明する。本実施の形態に係るマルチバンドアンテナは、共振する周波数帯域において、実施の形態１に係るマルチバンドアンテナ１と相違する。以下、本実施の形態に係るマルチバンドアンテナについて、実施の形態１に係るマルチバンドアンテナ１との相違点を中心に説明する。 (Embodiment 3)
The multi-band antenna according to the third embodiment will be described. The multi-band antenna according to the present embodiment is different from the multi-band antenna 1 according to the first embodiment in the resonating frequency band. Hereinafter, the multi-band antenna according to the present embodiment will be described focusing on the differences from the multi-band antenna 1 according to the first embodiment.
　［３－１．構成］
　まず、本実施の形態に係るマルチバンドアンテナの構成について、図１４を用いて説明する。図１４は、本実施の形態に係るマルチバンドアンテナ２０１の構成を示す平面図である。図１４には、マルチバンドアンテナ２０１の基板２４０の平面視における平面図が示されている。なお、図１４において、図１と同様に、マルチバンドアンテナ２０１の基板２４０の主面２４１に垂直な方向をＺ軸方向とし、Ｚ軸方向に垂直であって、互いに垂直な二つの方向をＸ軸方向及びＹ軸方向としている。 [3-1. Constitution]
First, the configuration of the multi-band antenna according to the present embodiment will be described with reference to FIG. FIG. 14 is a plan view showing the configuration of the multi-band antenna 201 according to the present embodiment. FIG. 14 shows a plan view of the substrate 240 of the multi-band antenna 201 in a plan view. In FIG. 14, as in FIG. 1, the direction perpendicular to the main surface 241 of the substrate 240 of the multi-band antenna 201 is the Z-axis direction, and the two directions perpendicular to the Z-axis direction and perpendicular to each other are X. Axial direction and Y-axis direction.
　マルチバンドアンテナ２０１は、第１周波数を含む第１周波数帯域の信号と、第１周波数より低い第２周波数を含む第２周波数帯域の信号とを送受信する。本実施の形態では、第１周波数帯域及び第２周波数帯域として、それぞれ、２．４ＧＨｚ帯及び９２０ＭＨｚ帯を用いる。図１４に示されるように、マルチバンドアンテナ２０１は、基板２４０と、入力端子２１６と、アンテナ部２１０と、接地部２２０とを備える。本実施の形態では、マルチバンドアンテナ２０１は、さらに接地端子２２６を備える。 The multi-band antenna 201 transmits and receives a signal in the first frequency band including the first frequency and a signal in the second frequency band including the second frequency lower than the first frequency. In the present embodiment, the 2.4 GHz band and the 920 MHz band are used as the first frequency band and the second frequency band, respectively. As shown in FIG. 14, the multi-band antenna 201 includes a substrate 240, an input terminal 216, an antenna portion 210, and a ground portion 220. In this embodiment, the multi-band antenna 201 further includes a ground terminal 226.
　基板２４０は、マルチバンドアンテナ２０１の基台となる部材である。基板２４０は、回路基板であり、基板２４０の一方の主面２４１に、アンテナ部２１０及び接地部２２０が配置される。 The board 240 is a member that serves as a base for the multi-band antenna 201. The board 240 is a circuit board, and an antenna portion 210 and a grounding portion 220 are arranged on one main surface 241 of the board 240.
　入力端子２１６は、基板２４０上に配置され、信号が入力される端子である。本実施の形態では、入力端子２１６には、マルチバンドアンテナ２０１が送信する高周波信号が入力される。また、入力端子２１６は、マルチバンドアンテナ２０１が受信した高周波信号を出力する出力端子としても機能する。また、入力端子２１６は、アンテナ部２１０に接続される。 The input terminal 216 is a terminal arranged on the board 240 to input a signal. In the present embodiment, the high frequency signal transmitted by the multi-band antenna 201 is input to the input terminal 216. The input terminal 216 also functions as an output terminal that outputs a high-frequency signal received by the multi-band antenna 201. Further, the input terminal 216 is connected to the antenna unit 210.
　接地端子２２６は、基板２４０上に配置され、グランドに接続される端子である。本実施の形態では、接地端子２２６は、基板２４０の主面２４１に配置され、接地部２２０に接続される。接地端子２２６の個数は特に限定されないが、本実施の形態では、２個である。 The ground terminal 226 is a terminal arranged on the board 240 and connected to the ground. In the present embodiment, the ground terminal 226 is arranged on the main surface 241 of the substrate 240 and is connected to the ground portion 220. The number of ground terminals 226 is not particularly limited, but is two in the present embodiment.
　アンテナ部２１０は、基板２４０上に配置され、入力端子２１６に接続される導電性部材である。本実施の形態では、アンテナ部２１０において第１周波数帯域の信号及び第２周波数帯域の信号が共振する。これにより、アンテナ部２１０から電波が放射される。アンテナ部２１０は、入力端子２１６側から順に、直列に接続された第１低インダクタンス部２１１、第１高インダクタンス部２１２及び第１先端部２１３を有する。第１低インダクタンス部２１１、第１高インダクタンス部２１２及び第１先端部２１３の電気長の和は、第２周波数の１／４波長である。これにより、アンテナ部２１０において第２周波数を含む第２周波数帯域の信号が共振する。 The antenna portion 210 is a conductive member arranged on the substrate 240 and connected to the input terminal 216. In the present embodiment, the signal in the first frequency band and the signal in the second frequency band resonate in the antenna unit 210. As a result, radio waves are radiated from the antenna unit 210. The antenna portion 210 has a first low inductance portion 211, a first high inductance portion 212, and a first tip portion 213 connected in series from the input terminal 216 side. The sum of the electrical lengths of the first low inductance portion 211, the first high inductance portion 212, and the first tip portion 213 is 1/4 wavelength of the second frequency. As a result, the signal in the second frequency band including the second frequency resonates in the antenna unit 210.
　アンテナ部２１０が入力端子２１６に接続される位置は特に限定されないが、本実施の形態では、入力端子２１６は、第１低インダクタンス部２１１の接地部２２０側の端部に配置される。より詳しくは、入力端子２１６は、第１低インダクタンス部２１１の接地部２２０側の端部のみに配置され、第１高インダクタンス部２１２及び第１先端部２１３には配置されない。なお、第１低インダクタンス部２１１の端部とは、例えば、第１低インダクタンス部２１１の接地部２０側の端から、第１低インダクタンス部２１１のＹ軸方向における長さの１０％以下の範囲の領域を意味する。 The position where the antenna portion 210 is connected to the input terminal 216 is not particularly limited, but in the present embodiment, the input terminal 216 is arranged at the end of the first low inductance portion 211 on the grounding portion 220 side. More specifically, the input terminal 216 is arranged only at the end of the first low inductance portion 211 on the grounding portion 220 side, and is not arranged at the first high inductance portion 212 and the first tip portion 213. The end of the first low inductance portion 211 is, for example, a range of 10% or less of the length of the first low inductance portion 211 in the Y-axis direction from the end of the first low inductance portion 211 on the grounding portion 20 side. Means the area of.
　本実施の形態では、第１低インダクタンス部２１１、第１高インダクタンス部２１２及び第１先端部２１３は、図１４のＹ軸方向に配列される。これにより、図１４のＹ軸方向が、アンテナ部２１０の長手方向、及び、アンテナ部２１０における信号の共振方向となる。図１４に示されるように、第１低インダクタンス部２１１、第１高インダクタンス部２１２及び第１先端部２１３の幅（つまり、共振方向に垂直な方向であって、基板２４０の主面２４１に平行な方向の寸法）は、同一である。 In the present embodiment, the first low inductance portion 211, the first high inductance portion 212, and the first tip portion 213 are arranged in the Y-axis direction of FIG. As a result, the Y-axis direction in FIG. 14 becomes the longitudinal direction of the antenna portion 210 and the resonance direction of the signal in the antenna portion 210. As shown in FIG. 14, the widths of the first low inductance portion 211, the first high inductance portion 212, and the first tip portion 213 (that is, the direction perpendicular to the resonance direction and parallel to the main surface 241 of the substrate 240). Dimensions) are the same.
　第１低インダクタンス部２１１は、アンテナ部２１０のうち、入力端子２１６に接続される部分である。第１低インダクタンス部２１１の一方の端部に入力端子２１６が接続され、他方の端部に第１高インダクタンス部２１２が接続される。第１低インダクタンス部２１１の電気長は、第１周波数の１／４波長である。第１低インダクタンス部２１１は、第１高インダクタンス部２１２より低いインダクタンスを有する。本実施の形態では、図１４に示されるように、第１低インダクタンス部２１１は、第１低インダクタンス部２１１は、線幅２．０ｍｍ、間隔２．０ｍｍ、長さ（図１４におけるＹ軸方向の寸法）２２ｍｍ、幅（図１４におけるＸ軸方向の寸法）７．５ｍｍのメアンダ形状を有する。このように、第１低インダクタンス部２１１はメアンダ形状を有するが、第１周波数帯域及び第２周波数帯域の信号に対してチョークコイルとして機能しない（つまり、信号を阻止しない）程度に低いインダクタンスを有する。なお、第１低インダクタンス部２１１は、メアンダ形状の部分の両端（つまり、Ｙ軸方向の両端）にメアンダ形状でない部分を有する。このメアンダ形状でない両端の二つの部分の合計の長さは、７ｍｍである。したがって、第１低インダクタンス部２１１のＹ軸方向における全長は、２９ｍｍとなる。 The first low inductance portion 211 is a portion of the antenna portion 210 connected to the input terminal 216. The input terminal 216 is connected to one end of the first low inductance portion 211, and the first high inductance portion 212 is connected to the other end. The electrical length of the first low inductance portion 211 is 1/4 wavelength of the first frequency. The first low inductance section 211 has a lower inductance than the first high inductance section 212. In the present embodiment, as shown in FIG. 14, the first low inductance portion 211 has a line width of 2.0 mm, an interval of 2.0 mm, and a length (Y-axis direction in FIG. 14). Dimension) 22 mm, width (dimension in the X-axis direction in FIG. 14) 7.5 mm, has a meander shape. As described above, the first low inductance portion 211 has a meander shape, but has a low inductance such that it does not function as a choke coil (that is, does not block the signal) with respect to the signals in the first frequency band and the second frequency band. .. The first low inductance portion 211 has portions that are not meander-shaped at both ends of the meander-shaped portion (that is, both ends in the Y-axis direction). The total length of the two portions at both ends that are not in the shape of a meander is 7 mm. Therefore, the total length of the first low inductance portion 211 in the Y-axis direction is 29 mm.
　第１高インダクタンス部２１２は、アンテナ部２１０のうち、第１低インダクタンス部２１１と第１先端部２１３との間に配置される部分であり、メアンダ形状を有する。第１高インダクタンス部２１２は、第１低インダクタンス部２１１より高いインダクタンスを有する。本実施の形態では、第１高インダクタンス部２１２のメアンダ形状は、第１低インダクタンス部２１１のメアンダ形状より、線幅及び間隔が小さい。これにより、第１高インダクタンス部２１２のインダクタンスが第１低インダクタンス部２１１より高くなる。本実施の形態では、第１高インダクタンス部２１２は、線幅０．１ｍｍ、間隔０．１ｍｍ、長さ（図１４におけるＹ軸方向の寸法）７．１ｍｍ、幅（図１４におけるＸ軸方向の寸法）７．５ｍｍのメアンダ形状を有する。第１高インダクタンス部２１２は、第１周波数帯域の信号に対してチョークコイルとして機能する。つまり、第１低インダクタンス部２１１に接続される入力端子２１６から入力された第１周波数帯域の信号に対するアンテナ部２１０の実効的な電気長は、第１低インダクタンス部２１１の電気長（第１周波数の１／４波長）となる。したがって、アンテナ部２１０において、第１周波数帯域の信号が共振する。なお、第１高インダクタンス部２１２は、第２周波数帯域の信号に対してチョークコイルとして機能しない程度に低いインダクタンスを有する。このため、第１高インダクタンス部２１２は、第２周波数帯域の信号を阻止しない。したがって、第２周波数帯域の信号は、アンテナ部２１０の第１低インダクタンス部２１１、第１高インダクタンス部２１２及び第１先端部２１３からなる経路において共振する。 The first high inductance portion 212 is a portion of the antenna portion 210 that is arranged between the first low inductance portion 211 and the first tip portion 213, and has a meander shape. The first high inductance section 212 has a higher inductance than the first low inductance section 211. In the present embodiment, the meander shape of the first high inductance portion 212 has a smaller line width and spacing than the meander shape of the first low inductance portion 211. As a result, the inductance of the first high inductance section 212 becomes higher than that of the first low inductance section 211. In the present embodiment, the first high inductance portion 212 has a line width of 0.1 mm, an interval of 0.1 mm, a length (dimensions in the Y-axis direction in FIG. 14) of 7.1 mm, and a width (in the X-axis direction in FIG. 14). Dimensions) It has a meander shape of 7.5 mm. The first high inductance portion 212 functions as a choke coil for signals in the first frequency band. That is, the effective electric length of the antenna unit 210 with respect to the signal of the first frequency band input from the input terminal 216 connected to the first low inductance unit 211 is the electric length of the first low inductance unit 211 (first frequency). 1/4 wavelength). Therefore, in the antenna unit 210, the signal in the first frequency band resonates. The first high inductance portion 212 has a low inductance that does not function as a choke coil with respect to a signal in the second frequency band. Therefore, the first high inductance portion 212 does not block the signal in the second frequency band. Therefore, the signal in the second frequency band resonates in the path including the first low inductance portion 211, the first high inductance portion 212, and the first tip portion 213 of the antenna portion 210.
　第１先端部２１３は、アンテナ部２１０のうち、入力端子２１６から共振方向に最も離れた端部に配置された部分である。第１先端部２１３の形状は特に限定されないが、本実施の形態では矩形状である。 The first tip portion 213 is a portion of the antenna portion 210 arranged at the end farthest from the input terminal 216 in the resonance direction. The shape of the first tip portion 213 is not particularly limited, but is rectangular in the present embodiment.
　接地部２２０は、基板２４０上に配置され、入力端子２１６と絶縁される導電性部材である。接地部２２０は、アンテナ部２１０に対して、共振方向に所定の距離だけ離隔して配置されている。アンテナ部２１０と接地部２２０との間隔は、例えば、０より大きく、３ｍｍ程度以下である。本実施の形態では、アンテナ部２１０と接地部２２０との間隔は、２．０ｍｍである。また、接地部２２０の幅（つまり、共振方向に垂直な方向であって、基板２４０の主面２４１に平行な方向の寸法）は、アンテナ部２１０の幅より広い。 The grounding portion 220 is a conductive member arranged on the substrate 240 and insulated from the input terminal 216. The grounding portion 220 is arranged at a distance from the antenna portion 210 by a predetermined distance in the resonance direction. The distance between the antenna portion 210 and the grounding portion 220 is, for example, greater than 0 and less than or equal to about 3 mm. In the present embodiment, the distance between the antenna portion 210 and the grounding portion 220 is 2.0 mm. Further, the width of the grounding portion 220 (that is, the dimension in the direction perpendicular to the resonance direction and parallel to the main surface 241 of the substrate 240) is wider than the width of the antenna portion 210.
　接地部２２０は、入力端子２１６側から順に、直列に接続された第２低インダクタンス部２２１、第２高インダクタンス部２２２及び第２先端部２２３を有する。また、第２低インダクタンス部２２１、第２高インダクタンス部２２２及び第２先端部２２３は、図１４のＹ軸方向に配列される。 The grounding portion 220 has a second low inductance portion 221, a second high inductance portion 222, and a second tip portion 223 connected in series from the input terminal 216 side. Further, the second low inductance portion 221 and the second high inductance portion 222 and the second tip portion 223 are arranged in the Y-axis direction of FIG.
　第２低インダクタンス部２２１、第２高インダクタンス部２２２及び第２先端部２２３の電気長の合計は、アンテナ部２１０から放射される第２周波数の電波の指向性が、アンテナ部２１０の長手方向（つまり、図１４のＹ軸方向）に垂直な面（つまり、図１４のＺＸ平面に平行な面）に沿って広がるように設定されている。 The total electrical lengths of the second low inductance section 221 and the second high inductance section 222 and the second tip section 223 are such that the directivity of the second frequency radio wave radiated from the antenna section 210 is the longitudinal direction of the antenna section 210. That is, it is set to spread along a plane perpendicular to the Y-axis direction of FIG. 14 (that is, a plane parallel to the ZX plane of FIG. 14).
　接地部２２０は、接地端子２２６と接続される。接地端子２２６の配置は特に限定されないが、本実施の形態では、接地端子２２６は、第２低インダクタンス部２２１のアンテナ部２１０側（つまり、入力端子２１６側）の端部に配置される。より詳しくは、二つの接地端子２２６は、第２低インダクタンス部２２１のアンテナ部２１０側の端部のみに配置され、第２高インダクタンス部２２２及び第２先端部２２３には配置されない。なお、第２低インダクタンス部２２１の端部とは、例えば、第２低インダクタンス部２２１のアンテナ部２１０側の端から、第２低インダクタンス部２２１の共振方向（図１４のＹ軸方向）における長さの１０％以下の範囲の領域を意味する。 The grounding portion 220 is connected to the grounding terminal 226. The arrangement of the ground terminal 226 is not particularly limited, but in the present embodiment, the ground terminal 226 is arranged at the end of the second low inductance portion 221 on the antenna portion 210 side (that is, the input terminal 216 side). More specifically, the two ground terminals 226 are arranged only at the end of the second low inductance portion 221 on the antenna portion 210 side, and are not arranged at the second high inductance portion 222 and the second tip portion 223. The end of the second low inductance portion 221 is, for example, the length of the second low inductance portion 221 in the resonance direction (Y-axis direction in FIG. 14) from the end of the second low inductance portion 221 on the antenna portion 210 side. It means an area in the range of 10% or less of the inductance.
　第２低インダクタンス部２２１は、接地部２２０のうち、アンテナ部２１０に最も近い位置に配置される部分である。第２低インダクタンス部２２１の一方の端部に接地端子２２６が接続され、他方の端部に第２高インダクタンス部２２２が接続される。第２低インダクタンス部２２１の電気長は、アンテナ部１０から放射される第１周波数の電波の指向性が、アンテナ部２１０の長手方向に垂直な面に沿って広がるように設定されている。 The second low inductance portion 221 is a portion of the grounding portion 220 that is arranged at the position closest to the antenna portion 210. The ground terminal 226 is connected to one end of the second low inductance portion 221 and the second high inductance portion 222 is connected to the other end. The electrical length of the second low inductance section 221 is set so that the directivity of the first frequency radio wave radiated from the antenna section 10 spreads along a plane perpendicular to the longitudinal direction of the antenna section 210.
　第２低インダクタンス部２２１は、第２高インダクタンス部２２２より低いインダクタンスを有する。本実施の形態では、図１４に示されるように、第２低インダクタンス部２２１は、矩形状の形状を有するが、第２低インダクタンス部２２１の形状は、これに限定されない。第２低インダクタンス部２２１の形状は、第２低インダクタンス部２２１のインダクタンスが、第１周波数及び第２周波数の信号に対してチョークコイルとして機能しない程度に低いインダクタンスを有するように設計されていればよい。 The second low inductance section 221 has a lower inductance than the second high inductance section 222. In the present embodiment, as shown in FIG. 14, the second low inductance portion 221 has a rectangular shape, but the shape of the second low inductance portion 221 is not limited to this. The shape of the second low inductance portion 221 is designed so that the inductance of the second low inductance portion 221 has such a low inductance that it does not function as a choke coil with respect to the signals of the first frequency and the second frequency. Good.
　第２高インダクタンス部２２２は、接地部２２０のうち、第２低インダクタンス部２２１と第２先端部２２３との間に配置される部分であり、メアンダ形状を有する。第２高インダクタンス部２２２は、第２低インダクタンス部２２１より高いインダクタンスを有する。第２高インダクタンス部２２２は、第１周波数帯域の信号に対してチョークコイルとして機能する。つまり、第２低インダクタンス部２２１に誘起される第１周波数帯域の信号に対する接地部２２０の実効的な電気長は、第２低インダクタンス部２２１の電気長となる。また、第２高インダクタンス部２２２は、第２周波数帯域の信号に対してチョークコイルとして機能しない程度に低いインダクタンスを有する。このため、第２高インダクタンス部２２２は、第２周波数帯域の信号を阻止しない。したがって、第２周波数帯域の信号に対する接地部２２０の実効的な電気長は、接地部２２０の第２高インダクタンス部２２２を含む経路の電気長を含む。 The second high inductance portion 222 is a portion of the grounding portion 220 that is arranged between the second low inductance portion 221 and the second tip portion 223, and has a meander shape. The second high inductance section 222 has a higher inductance than the second low inductance section 221. The second high inductance section 222 functions as a choke coil for signals in the first frequency band. That is, the effective electrical length of the grounding portion 220 with respect to the signal in the first frequency band induced in the second low inductance portion 221 is the electrical length of the second low inductance portion 221. Further, the second high inductance portion 222 has a low inductance that does not function as a choke coil with respect to a signal in the second frequency band. Therefore, the second high inductance section 222 does not block the signal in the second frequency band. Therefore, the effective electrical length of the grounding portion 220 with respect to the signal in the second frequency band includes the electrical length of the path including the second high inductance portion 222 of the grounding portion 220.
　第２高インダクタンス部２２２は、第２低インダクタンス部２２１の幅方向（図１４のＸ軸方向）の両端にそれぞれ接続される二つの高インダクタンス要素２２２ａ及び２２２ｂを有する。二つの高インダクタンス要素２２２ａ及び２２２ｂの間には、開口２２２ｃが形成されている。つまり、二つの高インダクタンス要素２２２ａ及び２２２ｂの間には、導電性部材が配置されない領域が形成される。なお、基板２４０の開口２２２ｃに対応する領域には、開口は設けられなくてもよい。二つの高インダクタンス要素２２２ａ及び２２２ｂの各々は、メアンダ形状を有する。また、二つの高インダクタンス要素２２２ａ及び２２２ｂは、互いに左右反転した構造を有する。したがって、二つの高インダクタンス要素２２２ａ及び２２２ｂの電気長は等しい。なお、本実施の形態では、マルチバンドアンテナ２０１の第２高インダクタンス部２２２の電気長を、二つの高インダクタンス要素２２２ａ及び２２２ｂの一方の電気長と定義する。また、二つの高インダクタンス要素２２２ａ及び２２２ｂのメアンダ形状部分における線幅及びピッチは、それぞれ、アンテナ部２１０の第１高インダクタンス部２１２のメアンダ形状部分における線幅及びピッチと同一であってもよい。 The second high inductance portion 222 has two high inductance elements 222a and 222b connected to both ends of the second low inductance portion 221 in the width direction (X-axis direction in FIG. 14), respectively. An opening 222c is formed between the two high inductance elements 222a and 222b. That is, a region in which the conductive member is not arranged is formed between the two high inductance elements 222a and 222b. An opening may not be provided in the region corresponding to the opening 222c of the substrate 240. Each of the two high inductance elements 222a and 222b has a meander shape. Further, the two high inductance elements 222a and 222b have a structure that is horizontally inverted from each other. Therefore, the electrical lengths of the two high inductance elements 222a and 222b are equal. In the present embodiment, the electric length of the second high inductance portion 222 of the multi-band antenna 201 is defined as the electric length of one of the two high inductance elements 222a and 222b. Further, the line width and pitch of the two high inductance elements 222a and 222b in the meander-shaped portion may be the same as the line width and pitch of the first high-inductance portion 212 of the antenna portion 210 in the meander-shaped portion, respectively.
　第２低インダクタンス部２２１においては、実施の形態１に係る第２低インダクタンス部２１と同様に、主に端縁に沿って、送受信する電波に対応する電流が流れる。このため、二つの高インダクタンス要素２２２ａ及び２２２ｂを接地部２２０の幅方向の端部に配置することにより、当該電流は、高インダクタンス要素２２２ａ及び高インダクタンス要素２２２ｂのいずれかを通る。 In the second low inductance section 221 as in the second low inductance section 21 according to the first embodiment, a current corresponding to radio waves transmitted and received flows mainly along the edge edge. Therefore, by arranging the two high inductance elements 222a and 222b at the widthwise ends of the grounding portion 220, the current passes through either the high inductance element 222a and the high inductance element 222b.
　第２先端部２２３は、接地部２２０のうち、アンテナ部２１０から共振方向に最も離れた端部に配置された部分である。本実施の形態では、第２先端部２２３は、矩形状の形状を有する。また、第２先端部２２３は、第２高インダクタンス部２２２の二つの高インダクタンス要素２２２ａ及び２２２ｂを接続する。 The second tip portion 223 is a portion of the grounding portion 220 arranged at the end portion farthest from the antenna portion 210 in the resonance direction. In the present embodiment, the second tip portion 223 has a rectangular shape. Further, the second tip portion 223 connects the two high inductance elements 222a and 222b of the second high inductance portion 222.
　［３－２．シミュレーション結果］
　次に、本実施の形態に係るマルチバンドアンテナ２０１のシミュレーション結果について図１５～図１７を用いて説明する。図１５及び図１６は、本実施の形態に係るマルチバンドアンテナ２０１の指向性のシミュレーション結果例を示すグラフである。図１５及び図１６には、それぞれ、第２高インダクタンス部２２２の各高インダクタンス要素のインダクタンスを３７．５ｎＨ及び４５ｎＨとした場合のシミュレーション結果が示されている。また、本シミュレーションにおいては、接地部２２０の幅Ｗｇ（つまり、共振方向に垂直な方向であって、基板４０の主面４１に平行な方向の寸法）を２０ｍｍとしている。各図においては、入力端子２１６に入力する第１周波数帯域及び第２周波数帯域の信号の周波数を、それぞれ、２．４５ＧＨｚ及び９２０ＭＨｚとした各場合の指向性が示されている。 [3-2. simulation result]
Next, the simulation results of the multi-band antenna 201 according to the present embodiment will be described with reference to FIGS. 15 to 17. 15 and 16 are graphs showing an example of a simulation result of directivity of the multi-band antenna 201 according to the present embodiment. 15 and 16 show simulation results when the inductance of each high inductance element of the second high inductance portion 222 is 37.5 nH and 45 nH, respectively. Further, in this simulation, the width Wg of the ground contact portion 220 (that is, the dimension in the direction perpendicular to the resonance direction and parallel to the main surface 41 of the substrate 40) is set to 20 mm. In each figure, the directivity in each case where the frequencies of the signals of the first frequency band and the second frequency band input to the input terminal 216 are 2.45 GHz and 920 MHz, respectively, is shown.
　図１５に示されるように、各高インダクタンス要素のインダクタンスが３７．５ｎＨの場合、周波数９２０ＭＨｚの信号に対して、共振方向に対して垂直な指向性を概ね実現できているが、周波数２．４５ＧＨｚの信号に対して、共振方向に対して垂直な指向性を実現できない。一方、図１６に示されるように、各高インダクタンス要素のインダクタンスが４５ｎＨの場合、周波数２．４５ＧＨｚ及び９２０ＭＨｚの両方の信号に対して、共振方向に対して垂直な指向性を概ね実現できている。同様のシミュレーションを行ったところ、各高インダクタンス要素のインダクタンスが４５ｎＨ以上の場合、周波数２．４５ＧＨｚ及び９２０ＭＨｚの両方の信号に対して、共振方向に対して垂直な指向性を概ね実現できることが分かった。 As shown in FIG. 15, when the inductance of each high inductance element is 37.5 nH, directivity perpendicular to the resonance direction can be generally realized for a signal having a frequency of 920 MHz, but the frequency is 2.45 GHz. The directivity perpendicular to the resonance direction cannot be realized for the signal of. On the other hand, as shown in FIG. 16, when the inductance of each high inductance element is 45 nH, directivity perpendicular to the resonance direction can be substantially realized for both signals having frequencies of 2.45 GHz and 920 MHz. .. When the same simulation was performed, it was found that when the inductance of each high inductance element is 45 nH or more, directivity perpendicular to the resonance direction can be generally realized for both signals having frequencies of 2.45 GHz and 920 MHz. ..
　以上のように、各高インダクタンス要素のインダクタンスが４５ｎＨ未満の場合、共振方向に対して垂直な指向性を実現できない。これは周波数２．４５ＧＨｚの信号に対しては、各高インダクタンス要素のチョークコイルとしての機能が十分に働かなかったことに起因すると考えられる。 As described above, when the inductance of each high inductance element is less than 45 nH, directivity perpendicular to the resonance direction cannot be realized. It is considered that this is because the function of each high inductance element as a choke coil did not work sufficiently for a signal having a frequency of 2.45 GHz.
　同様のシミュレーションを接地部２２０の幅Ｗｇが１５ｍｍ、１７．５ｍｍ、２２．５ｍｍ、２５ｍｍ及び２７．５ｍｍの各場合において行った結果について、図１７を用いて説明する。図１７は、本実施の形態に係る接地部２２０の幅Ｗｇと第２高インダクタンス部２２２の各高インダクタンス要素の最小インダクタンス値Ｌｍｉｎとの関係を示すグラフである。なお、最小インダクタンス値Ｌｍｉｎは、第１周波数帯域の信号に対して、共振方向に対して概ね垂直な指向性を実現するために必要な各高インダクタンス要素のインダクタンス値を意味する。図１７に示されるグラフにおいては、第１周波数帯域が２．４５ＧＨｚ帯である場合の最小インダクタンス値Ｌｍｉｎが示されている。 The results of performing the same simulation when the width Wg of the ground contact portion 220 is 15 mm, 17.5 mm, 22.5 mm, 25 mm, and 27.5 mm will be described with reference to FIG. FIG. 17 is a graph showing the relationship between the width Wg of the grounding portion 220 and the minimum inductance value Lmin of each high inductance element of the second high inductance portion 222 according to the present embodiment. The minimum inductance value Lmin means the inductance value of each high inductance element required to realize directivity substantially perpendicular to the resonance direction with respect to the signal in the first frequency band. In the graph shown in FIG. 17, the minimum inductance value Lmin when the first frequency band is the 2.45 GHz band is shown.
　図１７に示されるように、接地部２２０の幅Ｗｇが１５ｍｍ、１７．５ｍｍ、２０ｍｍ、２２．５ｍｍ、２５ｍｍ及び２７．５ｍｍの場合、それぞれ、各高インダクタンス要素の最小インダクタンス値Ｌｍｉｎは、５５ｎＨ、５０ｎＨ、４５ｎＨ、４５ｎＨ、４５ｎＨ及び３５ｎＨとなった。このことから、接地部２２０の幅Ｗｇが１５ｍｍ以上である場合、各高インダクタンス要素の最小インダクタンス値Ｌｍｉｎは、５５ｎＨ以上であれば十分であることが分かる。 As shown in FIG. 17, when the width Wg of the grounding portion 220 is 15 mm, 17.5 mm, 20 mm, 22.5 mm, 25 mm and 27.5 mm, the minimum inductance value Lmin of each high inductance element is 55 nH, respectively. It was 50 nH, 45 nH, 45 nH, 45 nH and 35 nH. From this, it can be seen that when the width Wg of the grounding portion 220 is 15 mm or more, the minimum inductance value Lmin of each high inductance element is 55 nH or more.
　（変形例など）
　以上、本開示のマルチバンドアンテナについて、実施の形態に基づいて説明したが、本開示は、上記実施の形態に限定されるものではない。本開示の趣旨を逸脱しない限り、当業者が思いつく各種変形を上記実施の形態に施したものも、本開示の範囲内に含まれてもよい。 (Modification example, etc.)
The multi-band antenna of the present disclosure has been described above based on the embodiment, but the present disclosure is not limited to the above-described embodiment. As long as it does not deviate from the purpose of the present disclosure, various modifications that can be thought of by those skilled in the art may be included in the scope of the present disclosure.
　例えば、マルチバンドアンテナ１として、二つの周波数帯域の信号を送受信するデュアルバンドの例を示したが、本開示のマルチバンドアンテナが送受信する周波数帯域は三つ以上であってもよい。例えば、第１周波数帯域及び第２周波数帯域に加えて、第１周波数より低く、第２周波数より高い第３周波数を含む第３周波数帯域を送受信するマルチバンドアンテナも実現できる。例えば、実施の形態１に係るマルチバンドアンテナ１において、第１低インダクタンス部１１と第１高インダクタンス部１２との間に、第１中インダクタンス部を挿入し、第２低インダクタンス部２１と第２高インダクタンス部２２との間に、第２中インダクタンス部を挿入することで、第１周波数帯域～第３周波数帯域の三つの周波数帯域の信号を送受信できるマルチバンドアンテナを実現できる。 For example, as the multi-band antenna 1, a dual band example of transmitting and receiving signals of two frequency bands has been shown, but the multi-band antenna of the present disclosure may transmit and receive three or more frequency bands. For example, a multi-band antenna that transmits and receives a third frequency band including a third frequency lower than the first frequency and higher than the second frequency in addition to the first frequency band and the second frequency band can be realized. For example, in the multi-band antenna 1 according to the first embodiment, the first middle inductance section is inserted between the first low inductance section 11 and the first high inductance section 12, and the second low inductance section 21 and the second By inserting the second middle inductance section between the high inductance section 22 and the high inductance section 22, it is possible to realize a multi-band antenna capable of transmitting and receiving signals in three frequency bands from the first frequency band to the third frequency band.
　ここで、第１中インダクタンス部は、第１低インダクタンス部１１よりインダクタンスが高く、第１高インダクタンス部１２よりインダクタンスが低い。また、第２中インダクタンス部は、第２低インダクタンス部２１よりインダクタンスが高く、第２高インダクタンス部２２よりインダクタンスが低い。第１低インダクタンス部１１及び第２低インダクタンス部２１は、第３周波数の信号に対してチョークコイルとして機能しない。第１中インダクタンス部及び第２中インダクタンス部は、第１周波数の信号に対してチョークコイルとして機能し、第２周波数及び第３周波数の信号に対してチョークコイルとして機能しない。第１高インダクタンス部１２及び第２高インダクタンス部２２は、第３周波数の信号に対してチョークコイルとして機能する。また、第１低インダクタンス部１１と第１中インダクタンス部との電気長の合計は、第３周波数の１／４波長である。 Here, the first middle inductance portion has a higher inductance than the first low inductance portion 11 and a lower inductance than the first high inductance portion 12. Further, the second middle inductance section has a higher inductance than the second low inductance section 21 and a lower inductance than the second high inductance section 22. The first low inductance section 11 and the second low inductance section 21 do not function as choke coils for signals of the third frequency. The first middle inductance portion and the second middle inductance portion function as choke coils for signals of the first frequency and do not function as choke coils for signals of the second frequency and the third frequency. The first high inductance section 12 and the second high inductance section 22 function as choke coils for signals of the third frequency. Further, the total electric length of the first low inductance portion 11 and the first middle inductance portion is 1/4 wavelength of the third frequency.
　また、上記実施の形態２では、アンテナモジュール１００を音響装置１０３において用いる例を示したが、他の装置において用いることも可能である。例えば、アンテナモジュール１００は、テレビジョン受像機などで用いられてもよい。 Further, in the second embodiment, the example in which the antenna module 100 is used in the audio device 103 is shown, but it can also be used in other devices. For example, the antenna module 100 may be used in a television receiver or the like.
　その他、本開示の趣旨を逸脱しない範囲で各実施の形態における構成要素及び機能を任意に組み合わせることで実現される形態なども本開示に含まれる。 In addition, the present disclosure also includes a form realized by arbitrarily combining the components and functions in each embodiment without departing from the purpose of the present disclosure.
　本開示のマルチバンドアンテナは、例えば、音響装置などにおいて用いられるアンテナモジュール用のアレイアンテナの一部として利用可能である。 The multi-band antenna of the present disclosure can be used as a part of an array antenna for an antenna module used in, for example, an audio device.
　１、１ａ、１ｂ、１ｃ、２０１、１００１　マルチバンドアンテナ
　１０、２１０　アンテナ部
　１１、２１１　第１低インダクタンス部
　１２、２１２　第１高インダクタンス部
　１３、２１３　第１先端部
　１６、２１６、Ｔ０　入力端子
　２０、２２０、１０２０　接地部
　２１、２２１　第２低インダクタンス部
　２２、２２２　第２高インダクタンス部
　２２ａ、２２ｂ、２２２ａ、２２２ｂ　高インダクタンス要素
　２２ｃ、２２２ｃ　開口
　２３、２２３　第２先端部
　２６、２２６　接地端子
　４０、１４０、２４０　基板
　４１、１４１、２４１　主面
　６１、６２、６３、７１、７２、７３、８１、８２　線路
　７１ｇ、７２ｇ、７３ｇ　接地配線
　７４、７４ｇ、７５ｇ、７６、７６ｇ、７７ｇ、７８、７８ｇ、７９ｇ、１９１、１９６ａ、１９６ｂ、１９６ｃ、１９７、１９８、１９９　端子
　８０　移相器
　８３、８４　コンデンサ
　８５、１９０　接地電極
　８６、８７　ＰＩＮダイオード
　１００、１００ａ、１０４　アンテナモジュール
　１０１　アレイアンテナ
　１０３　音響装置
　１０３ｃ　筐体
　１０６　３分配器
　Ｃｇ　コネクタグランド
　Ｃｎ　コネクタ
　ＣＰ１　第１接続点
　ＣＰ２　第２接続点
　ＣＰ３　第３接続点
　Ｌ１　第１伝送線路
　Ｌ１１　第１入力側線路
　Ｌ１２　第１出力側線路
　Ｌ２　第２伝送線路
　Ｌ２１　第２入力側線路
　Ｌ２２　第２出力側線路
　Ｌ３　第３伝送線路
　Ｌ３１　第３入力側線路
　Ｌ３２　第３出力側線路
　Ｒ１　第１抵抗
　Ｒ２　第２抵抗
　Ｒ３　第３抵抗
　Ｒ４　第４抵抗
　Ｓｐ０、Ｓｐ１、Ｓｐ２、Ｓｐ３、Ｓｐ４　スピーカ
　Ｔ１　第１出力端子
　Ｔ２　第２出力端子
　Ｔ３　第３出力端子
　Ｔｓ　制御端子 1, 1a, 1b, 1c, 201, 1001 Multi-band antenna 10, 210 Antenna part 11, 211 First low inductance part 12, 212 First high inductance part 13, 213 First tip part 16, 216, T0 Input terminal 20 , 220, 1020 Grounding part 21, 221 Second low inductance part 22, 222 Second high inductance part 22a, 22b, 222a, 222b High inductance element 22c, 222c Opening 23, 223 Second tip part 26, 226 Ground terminal 40, 140, 240 Substrates 41, 141, 241 Main surfaces 61, 62, 63, 71, 72, 73, 81, 82 Lines 71g, 72g, 73g Grounding wiring 74, 74g, 75g, 76, 76g, 77g, 78, 78g, 79g, 191, 196a, 196b, 196c, 197, 198, 199 terminals 80 Phase shifter 83, 84 Condenser 85, 190 Ground electrode 86, 87 PIN inductor 100, 100a, 104 Antenna module 101 Array inductance 103 Sound device 103c Housing 106 3 Distributor Cg Connector Ground Cn Connector CP1 1st Connection Point CP2 2nd Connection Point CP3 3rd Connection Point L1 1st Transmission Line L11 1st Input Side Line L12 1st Output Side Line L2 2nd Transmission Line L21 2nd Input Side line L22 2nd output side line L3 3rd transmission line L31 3rd input side line L32 3rd output side line R1 1st resistance R2 2nd resistance R3 3rd resistance R4 4th resistance Sp0, Sp1, Sp2, Sp3, Sp4 Speaker T1 1st output terminal T2 2nd output terminal T3 3rd output terminal Ts control terminal

Claims (7)

  1. 　基板と、
    　前記基板上に配置され、信号が入力される入力端子と、
    　前記基板上に配置され、かつ、前記入力端子に接続されるアンテナ部であって、前記入力端子側から順に、直列に接続された第１低インダクタンス部、メアンダ形状を有する第１高インダクタンス部及び第１先端部を有する導電性のアンテナ部と、
    　前記基板上に配置され、かつ、前記入力端子と絶縁される接地部であって、前記入力端子側から順に、直列に接続された第２低インダクタンス部、メアンダ形状を有する第２高インダクタンス部及び第２先端部を有する導電性の接地部とを備え、
    　前記第１低インダクタンス部は、前記第１高インダクタンス部よりインダクタンスが低く、
    　前記第２低インダクタンス部は、前記第２高インダクタンス部よりインダクタンスが低く、
    　前記第１低インダクタンス部の電気長は、第１周波数の１／４波長であり、
    　前記第１低インダクタンス部、前記第１高インダクタンス部及び前記第１先端部の電気長の和は、前記第１周波数より低い第２周波数の１／４波長である
    　マルチバンドアンテナ。     With the board
    An input terminal arranged on the board and into which a signal is input,
    An antenna portion arranged on the substrate and connected to the input terminal, the first low inductance portion connected in series from the input terminal side, the first high inductance portion having a meander shape, and the antenna portion. A conductive antenna portion having a first tip portion and
    A grounding portion arranged on the substrate and insulated from the input terminal, the second low inductance portion connected in series from the input terminal side, the second high inductance portion having a meander shape, and the second high inductance portion having a meander shape. With a conductive grounding part having a second tip,
    The first low inductance section has a lower inductance than the first high inductance section.
    The second low inductance section has a lower inductance than the second high inductance section.
    The electrical length of the first low inductance portion is 1/4 wavelength of the first frequency.
    A multi-band antenna in which the sum of the electrical lengths of the first low inductance portion, the first high inductance portion, and the first tip portion is 1/4 wavelength of the second frequency lower than the first frequency.
  2. 　前記第２低インダクタンス部の電気長は、前記アンテナ部から放射される前記第１周波数の電波の指向性が、前記アンテナ部の長手方向に垂直な面に沿って広がるように設定されている
    　請求項１に記載のマルチバンドアンテナ。     The electric length of the second low inductance portion is set so that the directivity of the first frequency radio wave radiated from the antenna portion spreads along a plane perpendicular to the longitudinal direction of the antenna portion. Item 1. The multi-band antenna according to Item 1.
  3. 　前記第２低インダクタンス部、前記第２高インダクタンス部及び前記第２先端部の電気長の合計は、前記アンテナ部から放射される前記第２周波数の電波の指向性が、前記アンテナ部の長手方向に垂直な面に沿って広がるように設定されている
    　請求項１又は２に記載のマルチバンドアンテナ。     The total of the electric lengths of the second low inductance portion, the second high inductance portion, and the second tip portion is such that the directivity of the second frequency radio wave radiated from the antenna portion is the longitudinal direction of the antenna portion. The multi-band antenna according to claim 1 or 2, which is set to spread along a plane perpendicular to.
  4. 　前記第２高インダクタンス部は、前記第２低インダクタンス部の幅方向の両端にそれぞれ接続される二つの高インダクタンス要素を有する
    　請求項１～３のいずれか１項に記載のマルチバンドアンテナ。     The multi-band antenna according to any one of claims 1 to 3, wherein the second high inductance portion has two high inductance elements connected to both ends in the width direction of the second low inductance portion.
  5. 　前記第２先端部は、前記二つの高インダクタンス要素を接続する
    　請求項４に記載のマルチバンドアンテナ。     The multi-band antenna according to claim 4, wherein the second tip portion connects the two high inductance elements.
  6. 　前記第１低インダクタンス部は、メアンダ形状を有し、前記第１高インダクタンス部よりインダクタンスが低い
    　請求項１～５のいずれか１項に記載のマルチバンドアンテナ。     The multi-band antenna according to any one of claims 1 to 5, wherein the first low inductance portion has a meander shape and has a lower inductance than the first high inductance portion.
  7. 　前記基板上に配置され、グランドに接続される接地端子をさらに備え、
    　前記接地端子は、前記第２低インダクタンス部の前記アンテナ部側の端部に接続される
    　請求項１～６のいずれか１項に記載のマルチバンドアンテナ。     Further provided with a ground terminal located on the board and connected to the ground
    The multi-band antenna according to any one of claims 1 to 6, wherein the ground terminal is connected to an end portion of the second low inductance portion on the antenna portion side.
PCT/JP2020/002036 2019-05-29 2020-01-22 Multiband antenna WO2020240916A1 (en)

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JP2019-100275 2019-05-29

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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2001185938A (en) * 1999-12-27 2001-07-06 Mitsubishi Electric Corp Two-frequency common antenna, multifrequency common antenna, and two-frequency and multifrequency common array antenna
JP2006033068A (en) * 2004-07-12 2006-02-02 Toshiba Corp Antenna and mobile wireless apparatus for mounting the antenna
WO2011080902A1 (en) * 2009-12-28 2011-07-07 パナソニック株式会社 Variable directional antenna device
US20140285387A1 (en) * 2013-03-24 2014-09-25 Delphi Deutschland Gmbh Broadband monopole antenna for vehicles for two frequency bands in the decimeter wavelength spectrum separated by a frequency gap
JP2015211425A (en) * 2014-04-30 2015-11-24 大井電気株式会社 Multiband antenna

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2001185938A (en) * 1999-12-27 2001-07-06 Mitsubishi Electric Corp Two-frequency common antenna, multifrequency common antenna, and two-frequency and multifrequency common array antenna
JP2006033068A (en) * 2004-07-12 2006-02-02 Toshiba Corp Antenna and mobile wireless apparatus for mounting the antenna
WO2011080902A1 (en) * 2009-12-28 2011-07-07 パナソニック株式会社 Variable directional antenna device
US20140285387A1 (en) * 2013-03-24 2014-09-25 Delphi Deutschland Gmbh Broadband monopole antenna for vehicles for two frequency bands in the decimeter wavelength spectrum separated by a frequency gap
JP2015211425A (en) * 2014-04-30 2015-11-24 大井電気株式会社 Multiband antenna

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