WO2020164099A1 - Procédé et appareil de séquencement - Google Patents

Procédé et appareil de séquencement Download PDF

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Publication number
WO2020164099A1
WO2020164099A1 PCT/CN2019/075192 CN2019075192W WO2020164099A1 WO 2020164099 A1 WO2020164099 A1 WO 2020164099A1 CN 2019075192 W CN2019075192 W CN 2019075192W WO 2020164099 A1 WO2020164099 A1 WO 2020164099A1
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WO
WIPO (PCT)
Prior art keywords
sequence
sequences
subset
reference signal
data
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PCT/CN2019/075192
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English (en)
Inventor
Chunli Liang
Chuangxin JIANG
Peng Hao
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Zte Corporation
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Priority to PCT/CN2019/075192 priority Critical patent/WO2020164099A1/fr
Priority to CN201980092249.0A priority patent/CN113439474A/zh
Publication of WO2020164099A1 publication Critical patent/WO2020164099A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2614—Peak power aspects
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J13/00—Code division multiplex systems
    • H04J13/0007—Code type
    • H04J13/0055—ZCZ [zero correlation zone]
    • H04J13/0059—CAZAC [constant-amplitude and zero auto-correlation]
    • H04J13/0062—Zadoff-Chu
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2602—Signal structure
    • H04L27/261—Details of reference signals
    • H04L27/2613—Structure of the reference signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J13/00—Code division multiplex systems
    • H04J13/0007—Code type
    • H04J13/0022—PN, e.g. Kronecker
    • H04J13/0029—Gold
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying

Definitions

  • This document is directed generally to wireless communications.
  • Wireless communication technologies are moving the world toward an increasingly connected and networked society.
  • the rapid growth of wireless communications and advances in technology has led to greater demand for capacity and connectivity.
  • Other aspects, such as energy consumption, device cost, spectral efficiency, and latency are also important to meeting the needs of various communication scenarios.
  • next generation systems and wireless communication techniques need to provide support for an increased number of users and devices, as well as support for higher data rates, thereby requiring user equipment to implement energy conservation techniques.
  • This document relates to methods, systems, and devices for generating sequences for reference signals in mobile communication technology, including 5th Generation (5G) and New Radio (NR) communication systems.
  • 5G 5th Generation
  • NR New Radio
  • a wireless communication method includes transmitting data, which is modulated using a pi/2-binary phase shift keying (BPSK) modulation, and a reference signal using a plurality of subcarriers, where the reference signal comprises a sequence from a subset of sequences that includes 30 sequences, each with a predetermined length, and where the subset of sequences include at least a first number of fixed sequences and a second number of selected sequences.
  • BPSK pi/2-binary phase shift keying
  • the above-described methods are embodied in the form of processor-executable code and stored in a computer-readable program medium.
  • a device that is configured or operable to perform the above-described methods is disclosed.
  • a wireless communication method includes transmitting data, wherein the data and the reference signal are modulated using a pi/2-binary phase shift keying (BPSK) modulation, wherein the reference signal comprises a sequence from a subset of sequences, wherein a size of the subset of sequences is greater than 30, wherein a length of each sequence of the subset of sequences is greater than 30, wherein the subset of sequences is generated using generic pseudo-random sequences defined by a length-31 Gold sequence, wherein transform precoding is enabled, and wherein the data and the reference signal are transmitted on a physical uplink shared channel (PUSCH) channel.
  • BPSK pi/2-binary phase shift keying
  • FIG. 1 shows an example of a base station (BS) and user equipment (UE) in wireless communication, in accordance with some embodiments of the presently disclosed technology.
  • BS base station
  • UE user equipment
  • FIG. 2 is a block diagram of an example implementation of a wireless communication apparatus.
  • FIG. 3 is a block diagram representation of a portion of an apparatus, in accordance with some embodiments of the presently disclosed technology.
  • FIG. 4 shows an example of a wireless communication method, in accordance with some embodiments of the presently disclosed technology.
  • 4G the 4th Generation mobile communication technology
  • LTE Long-term evolution
  • LTE-Advanced/LTE-A Long-Term Evolution Advanced
  • 5G the 5th Generation mobile communication technology
  • the Physical Uplink Control Channel (PUCCH) and the Physical Uplink Shared Channel (PUSCH) support pi/2-BPSK modulation in order to further reduce the peak-to-average power ratio (PAPR) of the signal.
  • Pi/2-BPSK is generated from the standard BPSK signal by multiplying the symbol sequence with a rotating phasor with phase increments per symbol period of pi/2.
  • Pi/2-BPSK has the same bit error rate performance as BPSK over a linear channel, however, it exhibits less envelope variation (i.e., PAPR) , making it more suitable for transmission with nonlinear channels. This improves the power-amplifier efficiency cost in the mobile terminal at lower data rates.
  • Pi/2-BPSK modulation is used to modulate the data portion of a signal
  • the reference signal (alternatively referred to herein as DMRS signal) still uses a Zadoff-Chu (ZC) sequence or a QPSK-based computer-generated sequence (referred to as CGS sequence)
  • ZC Zadoff-Chu
  • CGS sequence QPSK-based computer-generated sequence
  • Current implementations have shown that if the data portion uses pi/2-BPSK modulation and the reference signal uses a ZC sequence or a CGS sequence, the PAPR between the data portion and the reference signal is different, with the PAPR of the data portion being lower than that of the reference signal.
  • the power when the user transmits the PUSCH or the PUCCH, the power can be adjusted only for the entire PUSCH or the PUCCH; i.e., the transmission power of a certain symbol cannot be separately adjusted. Therefore, the PAPR of the data portion not being equal to the PAPR of the reference signal portion results in the low PAPR performance of the pi/2-BPSK modulation not being fully utilized, because the power adjustments are based on the higher PAPR of the reference signal. Accordingly, higher requirements are placed on the design of the reference signal. Sequence design with low peak-to-average ratio becomes an issue that is yet to be solved.
  • the sequence length of the reference signal is short (e.g., a sequence of length 6)
  • at least one of the 64 sequences exists, based on the possibility of cyclic shifting of another sequence. Therefore, after excluding sequences that are cyclically shifted from each other, the available sequences are further reduced. For this reason, for a sequence of length 6, a new sequence design needs to be considered.
  • FIG. 1 shows an example of a wireless communication system (e.g., an LTE, 5G or New Radio (NR) cellular network) that includes a BS 120 and one or more user equipment (UE) 111, 112 and 113.
  • the uplink transmissions (131, 132, 133) include ⁇ /2-BPSK modulated data portion and a reference signal that includes a sequence described by the presently disclosed technology.
  • the UE may be, for example, a smartphone, a tablet, a mobile computer, a machine to machine (M2M) device, a terminal, a mobile device, an Internet of Things (IoT) device, and so on.
  • M2M machine to machine
  • IoT Internet of Things
  • the present document uses section headings and sub-headings for facilitating easy understanding and not for limiting the scope of the disclosed techniques and embodiments to certain sections. Accordingly, embodiments disclosed in different sections can be used with each other. Furthermore, the present document uses examples from the 3GPP New Radio (NR) network architecture and 5G protocol only to facilitate understanding and the disclosed techniques and embodiments may be practiced in other wireless systems that use different communication protocols than the 3GPP protocols.
  • NR 3GPP New Radio
  • mathematical formulas may be used to generate sequences with the desired cross-correlation properties (an example of which will be described in a later section of this document) .
  • one or more sequences of a generated set of sequences may be screened out based on filtering the set of the sequences using criteria that include PAPR, auto-correlation, and cross-correlation thresholds.
  • the sequence search procedure can be summarized as follows:
  • Step 1 Set a PAPR threshold (denoted PAPR_Threshold) , exclude a sequence whose PAPR satisfies PAPR > PAPR_Threshold, and include the remaining sequence (s) in a set, S 1 .
  • a PAPR threshold denoted PAPR_Threshold
  • Step 2 This step can be implemented in any of the three ways discussed below.
  • Implementation 2 Set the predefined value for the variance of the sequence in frequency domain, denoted as FRVar_Threshold, exclude the sequences from sequence set S 1 whose variance in frequency domain exceed FRVar_Threshold. The sequence set of the remaining sequences is denoted as S 2 and goto Step 3.
  • Implementation 3 Set the predefined value for the variance of the sequence in frequency domain and the auto correlation at specific cyclic shifts, denoted as FRVar_Threshold and Auto_Threshold respectively, exclude the sequences from sequence set S 1 whose auto correlation exceed exceed Auto_Threshold or whose variance in frequency domain exceed FRVar_Threshold.
  • the sequence set of the remaining sequences is denoted as S 2 and go to Step 3.
  • Step 3 In sequence set S 2 , exclude one of the sequences in a sequence pair whose cross correlation equals to 1. The sequence set of the remaining sequences is denoted as S 3 ; and go to step 4.
  • Step 4 Set the predefined value for the cross correlation, denoted as Cross_Threshold, exclude one of the sequences in a sequence pair from sequence set S 2 whose cross correlation exceed Cross_Threshold.
  • the sequence set of the remaining sequences is denoted as S 4 . If the number of sequences in S 4 is less than the target sequence number M target , go to step 5, otherwise go to step 6.
  • Step 5 Increase the predefined value of PAPR_Threshold, Auto_Threshold, FRVar_Threshold or Cross_Threshold, and repeat to steps 1-4.
  • Step 6 Select the target sequences according to one of the following implementations:
  • Implementation 1 Reorder the sequences in S 4 based on their PAPR in an ascending order. Select the first M target sequences as the final target sequences.
  • Implementation 2 Reorder the sequences in S 4 based on their auto correlation at specific cyclic shift in an ascending order. Select the first M target sequences as the final target sequences.
  • Implementation 3 Reorder the sequences in S 4 based on the variance of the sequence in frequency domain in an ascending order. Select the first M target sequences as the final target sequences.
  • Implementation 4 Calculate the cross correlation of any two sequences in S 4 based on their PAPR in an ascending order. Exclude one of the sequence in the two sequences whose cross correlation is largest until the number of the remaining sequences equals to M target .
  • M target 30, i.e., 30 sequences may be generated.
  • the sequences can be represented as Herein, b u (n) ⁇ [-7, -5, -3, -1, 1, 3, 5, 7] representing the constellation points of the 8-PSK modulation format.
  • the PAPR may be calculated using the following formula:
  • PAPR 10 log 10 (
  • mean ( ⁇ ) represents the mean (or average) value.
  • the input for PAPR calculation is the time domain signal.
  • frequency domain spectrum shaping FDSS
  • FDSS frequency domain spectrum shaping
  • DMRS demodulation reference signal
  • the self/cross-correlation of the sequences may be calculated as:
  • xcorr_coeffs (cs_index) abs (sum ( (seq1 (cs_index) . *conj (seq2) ) ) /length (seq1)
  • length () represents the length
  • seq1 and seq2 are two sequences in the time domain
  • abs () represents the absolute value
  • sum () represents the summation
  • the relationship between the left or right shift can be interchanged.
  • xcorr_coeffs indicates the cyclic shift autocorrelation of the sequence
  • xcorr_coeffs indicates the cross-correlation of the two sequences.
  • the variance of the sequence in frequency domain may be calculated as:
  • seq_var var (abs (fft (seq) ) ) .
  • fft () represents the Discrete Fourier transform
  • seq is a sequence in the time domain
  • abs () represents the absolute value
  • var () represents the variance.
  • the frequency domain response of the sequence is desired to be flat.
  • the adjacent cyclic shift autocorrelation is desired to be small.
  • the sequence length is 6, in addition to the sequence itself, 5 other sequences can be generated by cyclic shift.
  • the sequence corresponding to 1 bit left and right is desired to be cyclically shifted from the original sequence.
  • Bit autocorrelation is also desired to be small.
  • Different sequence groups can be generated by setting different screening conditions. Preferably, two sets of screening conditions (e.g., with and without frequency domain spread shaping (FDSS) ) are set in the present patent document.
  • FDSS frequency domain spread shaping
  • Filter Condition 1 (Without FDSS) : PAPR ⁇ 2.3; For sequences related by ⁇ 1 cyclic shift, maximum value of Auto_corr ⁇ 0.2 and for 2 sequences, maximum value of xcorr_coeffs ⁇ 0.96.
  • Filter Condition 2 (Without FDSS) : PAPR ⁇ 2.0; For sequences related by ⁇ 1 cyclic shift, maximum value of Auto_corr ⁇ 0.3 and for 2 sequences, maximum value of xcorr_coeffs ⁇ 0.96.
  • Filter Condition 3 (Without FDSS) : PAPR ⁇ 2.3; For sequences related by ⁇ 1 cyclic shift, maximum value of Auto_corr ⁇ 0.3 and for 2 sequences, maximum value of xcorr_coeffs ⁇ 0.933.
  • Filter Condition 4 (With FDSS) : PAPR ⁇ 2.3; For sequences related by ⁇ 1 cyclic shift, maximum value of Auto_corr ⁇ 0.433 and for 2 sequences, maximum value of xcorr_coeffs ⁇ 0.96. Also, the variance of the sequence amplitude values does not exceed 0.6, after the sequence is transformed into the frequency domain.
  • the demodulation performance for PUSCH/PUCCH can also be considered.
  • the terminal transmits data and a reference signal for demodulating the data on L (L ⁇ 6) subcarriers of K (K ⁇ 2) symbols according to the received downlink control information, where the reference signal is transmitted on N subcarriers of one or more symbols of the above K symbols (the symbol of the transmission reference signal is a reference signal symbol) .
  • the downlink control information indicates that the terminal performs data modulation by using a pi/2-BPSK modulation mode
  • the sequence is sent on N subcarriers of the reference signal symbol after a discrete Fourier transform (DFT) .
  • DFT discrete Fourier transform
  • n 0, 1, 2, ..., N-1, b u (n) ⁇ [-7, -5, -3, -1, 1, 3, 5, 7] .
  • N 6
  • the values of u and b u (n) can be as shown in the various embodiments illustrated in Table 1, Table 2, Table 3, or Table 4.
  • the index u is determined by at least one of the following:
  • the sequence index u is determined according to the cell identifier
  • the sequence index u is determined according to the indication signaling of the base station.
  • the PAPR and cross-correlation of the sequence set in Table 1 have the following properties:
  • the sequence set includes at least one of the following sequences:
  • the PAPR and cross-correlation of the sequence set in Table 2 have the following properties:
  • the sequence set includes at least one of the following sequences:
  • the PAPR and cross-correlation of the sequence set in Table 3 have the following properties:
  • the PAPR and cross-correlation of the sequence set in Table 4 have the following properties:
  • the sequence set includes at least one of the following sequences:
  • mappings of u and b u (n) have been used to provide a further understanding of the disclosed technology. These examples are used to explain the technology rather than limiting its scope.
  • Embodiments of the disclosed technology advantageously result in a low peak-to-average ratio, a small cubic metric, and high power amplifier efficiency.
  • the method when the sequence index used by the neighboring cells is different, the method further has the effect of reducing inter-cell interference and improving overall system performance.
  • FIG. 2 depicts a block diagram representing an architecture of a communication apparatus such as a user equipment (UE) terminal or wireless communication apparatus 200.
  • a terminal 200 can include one or multiple processor electronics 210 such as a microprocessor that implements one or more of the wireless techniques presented in this document.
  • the terminal 200 can include transmitter electronics 215 and receiver electronics 220 to send and/or receive wireless signals over one or more communication interfaces such as antenna 220.
  • transmitter electronics 215 and receiver electronics 220 can be integrated into a single electronics transceiver unit or module.
  • the terminal 200 can include other communication interfaces for transmitting and receiving data.
  • the terminal 200 can include one or more memories 205 configured to store information such as data and/or instructions related to the methods disclosed herein.
  • the processor electronics 210 can include at least a portion of the transceiver electronics 215. In some embodiments, at least some of the disclosed techniques, modules or functions are implemented using the sequence generation module 225.
  • FIG. 3 is a block diagram representation of a portion of an apparatus, in accordance with some embodiments of the presently disclosed technology.
  • FIG. 3 shows DMRS sequence generator 304 and pi/2-BPSK module 302 coupled to DFT module 306.
  • DFT module 306 is coupled to frequency mapping module 308 which is coupled to IFFT module 310.
  • the output of the DMRS sequence generator 304 are 8-PSK symbols.
  • DMRS symbols can be directly inserted in the frequency domain.
  • Computer-generated sequences (CGS) for DMRS symbols can be inserted in the time domain in implementations when transform precoding is enabled and PUSCH symbols are modulated with pi/2-BPSK.
  • FIG. 3 shows DMRS sequence generator 304 and pi/2-BPSK module 302 coupled to DFT module 306.
  • DFT module 306 is coupled to frequency mapping module 308 which is coupled to IFFT module 310.
  • the output of the DMRS sequence generator 304 are 8-PSK symbols.
  • DMRS symbols can be directly
  • DMRS symbols are generated before a DFT operation.
  • DMRS sequences can also be modulated by pi/2-BPSK modulation in the same manner as PUSCH channel symbols.
  • the PAPR of DMRS symbols can be kept at the same level as the PUSCH channel symbols.
  • DMRS sequences before pi/2-BPSK modulation can be composed of a set of bits, the value of each bit being 0 or 1.
  • each bit, e.g. b (i) of DMRS sequence is modulated by ⁇ /2-BPSK modulation, bit is mapped to complex-valued modulation symbol d (i) according to the following formula
  • b (i) can be generated using generic pseudo-random sequences defined by a length-31 Gold sequence.
  • the output Gold sequence c (n) can be generated based on a sequence initialization value c init . Then b (i) can be replaced by c (n) , wherein i and n are the index of DMRS sequence.
  • n SCID The value of n SCID can be initialized according to one of the following implementations discussed below.
  • n SCID is dynamically indicated by the 1-bit DCI ‘DMRS sequence initialization’ field. However, there is no such field in DCI for DFT-s-OFDM.
  • the value of n SCID can be set to zero.
  • gNB can choose one value of n SCID and send the value to UE if the selected n SCID value can introduce better flatness in the frequency domain. Therefore, in order to get greater flexibility, one new bit n SCID field can be introduced in DCI in the case when transform precoding is enabled, i.e. for DFT-s-OFDM. However, the new bit can result in a new DCI format when transform precoding is enabled.
  • a DMRS port indication field e.g., the ‘Antenna ports’ field in DCI can be used to indicate the value of n SCID when the PUSCH channel symbols are modulated by pi/2-BPSK.
  • the 2 bit and/or 4 bit ‘Antenna ports’ field are used to indicate DMRS port information for DFT-s-OFDM.
  • Implementation 4 for initializing the value of n SCID the maximum number of DMRS ports can be limited to 1 when the PUSCH channel symbols are demodulated with pi/2-BPSK. In these implementations, less number of bits (sometimes no bits) are needed for DMRS port indication.
  • the values of n SCID can be from 0 to N. N can be larger than 1, e.g. 2, 3, 4, 5, 6, or 7.
  • Implementation 5 for initializing the value of n SCID the DMRS port information and the value of can be jointly encoded, e.g., as shown in Tables 10 and 11 when the PUSCH channel symbols are demodulated with pi/2-BPSK.
  • the interpretation of the DMRS port indication field in DCI is based on MCS indication. If the MCS field in the DCI indicates pi/2-BPSK modulation order, the DMRS port indication field can be used to indicate the value of DMRS sequence initialization. In some implementations, the interpretation of the DMRS port indication field in the DCI is based on the MCS field, transform precoding and a higher layer parameter. If the higher layer parameter indicates the new DMRS sequence (pi/2-BPSK based sequences) is used (before DFT operation) , transform precoding is enabled, and MCS field in the DCI indicates pi/2-BPSK modulation order, the DMRS port indication field can be used to indicate the value of DMRS sequence initialization.
  • Rel-15 DMRS sequences can be used when transform precoding is enabled, and the MCS field in the DCI can indicate pi/2-BPSK modulation order. That is because legacy UEs or some new UEs may not be able to support the new DMRS sequences.
  • FIG. 4 shows an example of a wireless communication method 400 for generating sequences for reference signals in mobile communication technology.
  • the method 400 includes, at step 410, transmitting data, which is modulated using a pi/2-binary phase shift keying (BPSK) modulation, and a reference signal, which comprises a sequence from a subset of sequences of size 30, using a plurality of subcarriers.
  • BPSK pi/2-binary phase shift keying
  • a cross-correlation between a first sequence and a second sequence is less than a threshold.
  • the data and the reference signal are transmitted on a physical uplink shared channel (PUSCH) or a physical uplink control channel (PUCCH) .
  • the data comprises uplink traffic data and uplink control information.
  • the reference signal is used to demodulate the data.
  • the sequences described and constructed by embodiments of the disclosed technology advantageously enable improved demodulation performance due to their PAPR and CM correlation properties.
  • a computer-readable medium may include removable and non-removable storage devices including, but not limited to, Read Only Memory (ROM) , Random Access Memory (RAM) , compact discs (CDs) , digital versatile discs (DVD) , etc. Therefore, the computer-readable media can include a non-transitory storage media.
  • program modules may include routines, programs, objects, components, data structures, etc. that perform particular tasks or implement particular abstract data types.
  • Computer-or processor-executable instructions, associated data structures, and program modules represent examples of program code for executing steps of the methods disclosed herein. The particular sequence of such executable instructions or associated data structures represents examples of corresponding acts for implementing the functions described in such steps or processes.
  • a hardware circuit implementation can include discrete analog and/or digital components that are, for example, integrated as part of a printed circuit board.
  • the disclosed components or modules can be implemented as an Application Specific Integrated Circuit (ASIC) and/or as a Field Programmable Gate Array (FPGA) device.
  • ASIC Application Specific Integrated Circuit
  • FPGA Field Programmable Gate Array
  • DSP digital signal processor
  • the various components or sub-components within each module may be implemented in software, hardware or firmware.
  • the connectivity between the modules and/or components within the modules may be provided using any one of the connectivity methods and media that is known in the art, including, but not limited to, communications over the Internet, wired, or wireless networks using the appropriate protocols.

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  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
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  • Mobile Radio Communication Systems (AREA)

Abstract

La présente invention concerne des procédés, des systèmes et des dispositifs de séquencement pour des signaux de référence dans une technologie de communication mobile. Un procédé donné à titre d'exemple pour une communication mobile comprend la transmission de données, qui sont modulées à l'aide d'une modulation par déplacement de phase binaire (BPSK) de pi/2, et d'un signal de référence à l'aide d'une pluralité de sous-porteuses, le signal de référence comprenant une séquence d'un sous-ensemble de séquences qui contient 30 séquences qui ont chacune une longueur prédéfinie, et le sous-ensemble de séquences comprenant au moins un premier nombre de séquences fixes et un second nombre de séquences sélectionnées. Le procédé permet en outre de construire les séquences selon un procédé mis en œuvre par ordinateur, qui ont des propriétés de rapport de puissance crête à moyenne (PAPR) faible, pour une longueur de séquence N = 6.
PCT/CN2019/075192 2019-02-15 2019-02-15 Procédé et appareil de séquencement WO2020164099A1 (fr)

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WO2019001287A1 (fr) * 2017-06-30 2019-01-03 华为技术有限公司 Procédé et dispositif de transmission
CN109219948A (zh) * 2017-08-11 2019-01-15 华为技术有限公司 一种信号处理方法及装置
CN109245844A (zh) * 2017-06-30 2019-01-18 华为技术有限公司 无线通信方法、装置及系统

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CN109150782A (zh) * 2017-06-16 2019-01-04 维沃移动通信有限公司 一种pucch的发送方法、检测方法及设备

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Publication number Priority date Publication date Assignee Title
CN107466054A (zh) * 2016-06-06 2017-12-12 中兴通讯股份有限公司 干扰源小区的定位方法、装置及基站
WO2019001287A1 (fr) * 2017-06-30 2019-01-03 华为技术有限公司 Procédé et dispositif de transmission
CN109245844A (zh) * 2017-06-30 2019-01-18 华为技术有限公司 无线通信方法、装置及系统
CN109219948A (zh) * 2017-08-11 2019-01-15 华为技术有限公司 一种信号处理方法及装置

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