WO2019213976A1

WO2019213976A1 - Signal sending method and apparatus, and signal receiving method and apparatus

Info

Publication number: WO2019213976A1
Application number: PCT/CN2018/086618
Authority: WO
Inventors: 李德建; 斯特凡诺布齐
Original assignee: 华为技术有限公司
Priority date: 2018-05-11
Filing date: 2018-05-11
Publication date: 2019-11-14

Abstract

Provided are a signal sending method and apparatus, and a signal receiving method and apparatus, wherein same relate to the field of communications and are capable of being used for combining and designing MIMO technology and UFMC signal modulation technology in a millimeter-wave band. The signal receiving method comprises: by means of Ｎ_R ^RF receiving antennas, a receiving end receiving a first universal filtered multicarrier (UFMC) signal Y_BB, wherein the first UFMC signal comprises at least one UFMC symbol, and each UFMC symbol comprises k sub-carriers; the receiving end carrying out N-point FFT on C sampling points, included in the first UFMC signal, of each of the receiving antennas to obtain a second UFMC signal Z_BB; the receiving end selecting J sampling points from among D sampling points, included in the second UFMC signal, of each receiving antenna from among the N_R ^RF receiving antennas to obtain a third UFMC signal Z_BB,n, wherein D is greater than C, and J is a positive integer less than D; and the receiving end carrying out an operation on the third UFMC signal based on an adaptive algorithm to obtain an estimated value ŝ for sending a signal. The embodiments of the present application are applied to a communication system using UFMC modulation and MIMO.

Description

Signal transmitting and receiving method and device

Technical field

The present application relates to the field of communications, and in particular, to a signal transmitting and receiving method and apparatus.

Background technique

Due to the rapid development of various types of wireless communication and wireless applications, low-band spectrum resources have become very tight. At the same time, in order to obtain a larger transmission bandwidth, various RF devices are also necessary to adjust to a better operating frequency. Therefore, the future fifth-generation mobile communication (5-Generation, 5G) technology must be extended to high frequency bands, especially the millimeter wave frequency band. This frequency band is rich in spectrum resources and has continuous large bandwidth, which can meet the needs of short-distance high-speed transmission. In order to overcome the high path loss in the high frequency band, devices in the millimeter wave band usually use multiple input multiple output (MIMO) technology to achieve analog beamforming, that is, multiple transmissions are used at the transmitting end and the receiving end respectively. The antenna and the receiving antenna achieve beam alignment. In order to obtain a higher reachable transmission rate in the millimeter wave band, Hybrid Beamforming can be employed at the transmitting end and the receiving end, wherein the hybrid beamforming includes analog beamforming coding and digital precoding. In order to further improve the spectrum utilization, a Universal Filtered Multicarrier (UFMC) modulation technique can be used to transmit signals in the millimeter wave band. As shown in FIG. 1 , the UFMC modulation technology divides all subcarriers into multiple subcarrier groups, and multiple subcarriers in one subcarrier group are adjacent subcarriers, and subcarriers of different subcarrier groups do not overlap. In the UFMC modulation process, filtering is required for each group of subcarriers.

When using UFMC modulation technology in the millimeter wave band, it is necessary to analyze and design the MIMO technology of analog beamforming or hybrid beamforming and UFMC signal modulation. In the prior art, UFMC and multi-antenna technology in the millimeter wave band have not been applied. The combination of the design of the sending and receiving processes.

Summary of the invention

The embodiment of the present application provides a signal transmitting and receiving method and device, and provides a design of a sending and receiving process combining UFMC modulation and multi-antenna technology in a millimeter wave band.

In a first aspect, an embodiment of the present application provides a signal receiving method, including: receiving a

Receiving antennas receive a first general-purpose filtered multi-carrier UFMC signal Y _BB ; wherein the first UFMC signal includes at least one UFMC symbol, and each UFMC symbol includes k sub-carriers,

And k is an integer greater than or equal to 1; the receiving end is

Each of the receiving antennas has a C sample of the C samples included in the first UFMC signal and performs a fast Fourier transformation (FFT) to obtain a second UFMC signal Z _BB , where C is greater than An integer of k, N is an integer greater than k, C is less than or equal to N;

Each of the receiving antennas selects J sampling points among the D sampling points included in the second UFMC signal to obtain a third UFMC signal Z _BB,n , D is greater than C, and J is a positive integer smaller than D; Calculating the estimated value of the transmitted signal by calculating the third UFMC signal based on the adaptive algorithm

Wherein, the signal matrix Z _BB corresponding to the second UFMC signal is

Dimension, the signal matrix Z _BB,n of the third UFMC signal is

dimension. Where C can be k+L+L _ch –2. when

When it is greater than 1, the sampling point of the signal is

The sampling antennas are sampled at the same sampling time.

a sampling point vector formed by sampling points; each sampling point of the first UFMC signal, the second UFMC signal, and the third UFMC signal respectively refers to each column vector of the corresponding signal matrix, for example, each of the third UFMC signals The sample points correspond to each column vector of Z _BB,n .

The embodiment of the present application provides a signal receiving method, where a receiving end can receive a first UFMC signal Y _BB through multiple receiving antennas, and a receiving end can perform N point FFT on Y _BB to obtain a second UFMC signal Z _BB , and lower the second Obtain an estimated value of the transmitted signal based on the number of sampling points included in the UFMC signal Z _BB

The first signal is a UFMC-MIMO signal sent by the transmitting end, and the first UFMC signal Y _BB includes a multipath effect, and the amplitude and phase changes are superimposed, and the original signal of the transmitting end needs to be eliminated. Estimated value of the transmitted signal

It refers to the signal that the receiving end restores the transmitted signal with multipath effect. Therefore, the signal receiving method provided by the embodiment of the present application can be used for receiving and correspondingly processing a MIMO-UFMC signal in a millimeter wave band. It should be noted that the estimated value of the transmitted signal can be calculated based on the adaptive algorithm by reducing the number of sampling points included in the UFMC signal.

Reduce the computational complexity of the receiver. Moreover, the computational complexity required by the signal receiving method provided by the embodiment of the present application may be

Multiplying the complex number, the computational overhead of the receiver is linear with the number of subcarriers k, and only

Cube. Compared with the prior art, the calculation cost of obtaining the estimated value of the signal on all subcarriers by the traditional MMSE algorithm is the order of the number of cubics of the number of subcarriers k, and the complexity of the equalization algorithm proposed in the embodiment of the present application is significantly decreased. .

In a possible implementation, the receiving end

Each of the receiving antennas selects J sampling points among the D sampling points included in the second UFMC signal to obtain a third UFMC signal Z _{BB, n} includes:

when

And

Time,

when

When I _min =1, I _max =J;

when

When I _min = 2k-J+1, I _max = 2k;

The third UFMC signal Z _{BB,n is} as follows:

, N represents an arbitrary sampling points D a sampling point number, I _min represents a lower limit of the sampling point of the reception end determines the Z _BB, I _max represents the upper limit of the sampling point of the reception end determines the Z _BB,

Represents the range of sample points that J sample points are included in D sample points.

After simulation evaluation, the 2k point FFT can reduce the computational overhead of the receiver because it can concentrate the contribution of the signal on a part of the pre-acknowledged subcarriers, and obtain the signal estimation values of all subcarriers corresponding to the transmitted signal.

In a possible implementation manner, the receiving end calculates the estimated value of the transmitted signal by calculating the third UFMC signal based on the adaptive algorithm, including: the vectorized signal z _{BB, n} and the receiving end according to the third signal Z _BB,n A parameter d _RC (n) determines the estimated value of the transmitted signal

As follows:

The first parameter d _RC (n) as follows:

among them,

Indicates the number of samples used to calculate the time average, S ₁ (:, n) represents the value of the transmitted signal at the nth time, and H represents the conjugate transpose operator.

Compared with the prior art, the calculation of the estimated value of the signal on all the subcarriers by the conventional MMSE algorithm is on the order of the cube of the number of subcarriers k. The signal receiving method provided by the embodiment of the present application can reduce the calculation of the receiving end. Complexity, so that the computational complexity required to obtain an estimate of the signal on all subcarriers is only

Submultiple multiplication, the computational overhead of the receiver is linear with the number of subcarriers k, and is only the data window dimension

Cube. Therefore, the complexity of the equalization algorithm proposed in the embodiment of the present application is significantly reduced.

In a possible implementation, the adaptive algorithm includes Minimum mean square error estimation (MMSE), Normalized Least Mean Squares (NLMS), Recursive Least (Recursive Least) Squares, RLS) and other algorithms.

In a possible implementation manner, the receiving end pair

Before each of the receiving antennas performs the N-point fast Fourier transform FFT to obtain the second UFMC signal Z _BB in the C-sampling point included in the first UFMC signal, the method further includes: the receiving end discarding the first UFMC signal The last S sample points; wherein S is determined according to the length parameter of the filter and/or the length parameter of the channel impulse response when the UFMC signal is modulated. In this way, when an FFT greater than k points is used, such as a 2k point FFT, it is convenient to use an equal-sized FFT.

In a possible implementation manner, the receiving end passes

Before receiving the first general-purpose filtered multi-carrier UFMC signal Y _BB , the method further includes: the receiving end sends an analog pre-coded coding matrix or beam number to the transmitting end, and the coding matrix is determined according to the result of the simulated beamforming training. Or, the receiving end sends an analog precoding coding matrix and a digital precoding matrix to the transmitting end. When the UFMC signal is transmitted in the millimeter wave band, analog precoding can improve the antenna gain and increase the link budget.

In a second aspect, an embodiment of the present application provides a receiving apparatus, including: a receiving unit, configured to pass

And k is an integer greater than or equal to 1; processing unit for

Each of the receiving antennas performs N-point fast Fourier transform FFT on the C sampling points included in the first UFMC signal to obtain a second UFMC signal Z _BB , where C is an integer greater than k, and N is greater than k Integer, C is less than or equal to N; processing unit, also used to

Each of the receiving antennas selects J sampling points among the D sampling points included in the second UFMC signal to obtain a third UFMC signal Z _BB,n , D is greater than C, and J is a positive integer smaller than D; And is also used to calculate the estimated value of the transmitted signal by calculating the third UFMC signal based on the adaptive algorithm.

In a possible implementation, the processor of the receiving device can be used to perform the following operations:

when

And

Time,

when

When I _min =1, I _max =J;

when

When I _min = 2k-J+1, I _max = 2k;

The third UFMC signal Z _{BB,n is} as follows:

The estimated _{value, n} for a vector signal z _{BB, n,} and the first parameter d _RC (n) is determined in accordance with a transmission signal of the third signal Z _BB:] In one possible implementation, the processing unit for

As follows:

The first parameter d _RC (n) is as follows:

among them,

In a possible implementation manner, the adaptive algorithm includes an MMSE algorithm, an NLMS algorithm or an RLS algorithm.

In a possible implementation, the processing unit is used to

The processing unit is further configured to: after each of the receiving antennas, the C-sampling points included in the first UFMC signal are subjected to the N-point fast Fourier transform FFT to obtain the second UFMC signal Z _BB , the processing unit is further configured to: discard the first UFMC signal S sampling points; wherein S is determined according to a length parameter of the filter and/or a length parameter of the channel impulse response when the UFMC signal is modulated.

In a possible implementation, the method further includes: a sending unit, configured to send, to the sending end, an encoding matrix or a beam number of the analog precoding, where the encoding matrix is determined according to a result of the simulated beamforming training; or, sending to the transmitting end Analog precoding coding matrix and digital precoding matrix.

For the technical effects of the second aspect and various alternative implementations, reference may be made to the technical effects of the first aspect and various alternative implementations, and details are not described herein again.

In a third aspect, an embodiment of the present application provides a receiving apparatus, including: a receiver, configured to pass

And k is an integer greater than or equal to 1; the processor is used to

Each of the receiving antennas performs N-point fast Fourier transform FFT on the C sampling points included in the first UFMC signal to obtain a second UFMC signal Z _BB , where C is an integer greater than k, and N is greater than k Integer, C is less than or equal to N; processor, also used to

when

And

Time,

when

When I _min =1, I _max =J;

when

When I _min = 2k-J+1, I _max = 2k;

The third UFMC signal Z _{BB,n is} as follows:

In one possible implementation, the processor is configured _{to:, n} signal vector z _{BB, n,} and the first parameter d _RC (n) to determine an estimated value of the transmission signal according to a third signal Z _BB

As follows:

The first parameter d _RC (n) is as follows:

among them,

Indicates the number of samples used to calculate the time average, and S ₁ (:, n) represents the value of the transmitted signal at the nth time.

In a possible implementation, the processor is used to

The processor is further configured to: after each of the receiving antennas, the C-sample points included in the first UFMC signal are subjected to the N-point fast Fourier transform FFT to obtain the second UFMC signal Z _BB , the processor is further configured to: discard the first UFMC signal S sampling points; wherein S is determined according to a length parameter of the filter and/or a length parameter of the channel impulse response when the UFMC signal is modulated.

In a fourth aspect, an embodiment of the present application provides a device, which is in the form of a product of a chip. The device includes a processor and a memory, and the memory is coupled to the processor to save necessary program instructions of the device. And data for executing the program instructions stored in the memory such that the apparatus performs the functions of the receiving apparatus in the above method.

In a fifth aspect, the embodiment of the present application provides a receiving apparatus, which can implement the functions performed by the receiving apparatus in the foregoing method embodiment, and the functions can be implemented by using hardware or by executing corresponding software by hardware. The hardware or software includes one or more modules corresponding to the above functions.

In one possible design, the receiving device includes a processor and a communication interface configured to support the receiving device to perform a corresponding function in the above method. The communication interface is used to support communication between the receiving device and other network elements. The receiving device can also include a memory for coupling with the processor that retains the program instructions and data necessary for the receiving device.

In a sixth aspect, an embodiment of the present application provides a computer readable storage medium, including instructions, when executed on a computer, causing a computer to perform any one of the methods provided by the first aspect.

In a seventh aspect, an embodiment of the present application provides a computer program product comprising instructions, which when executed on a computer, cause the computer to perform any one of the methods provided by the first aspect.

In an eighth aspect, an embodiment of the present application provides a signal sending method, including: performing, by a transmitting end, performing general-purpose filtering, multi-carrier UFMC modulation on at least one spatial stream or a space-time stream to obtain a signal.

Transmitter pair signal

Perform analog precoding to get the signal

The sender sends a signal to the receiver

The embodiment of the present application provides a signal sending method, which is capable of performing UFMC modulation and analog precoding on at least one spatial stream or space-time stream to be sent to obtain a signal.

signal

It can be sent to the receiving end through multiple transmitting antennas on the transmitting end, and the MIMO-UFMC signal can be transmitted in the millimeter wave frequency band. Further, the signal transmission method adopts a modulation method (MIMO-UFMC modulation) combining a UFMC signal and an analog/mixing beamforming for a millimeter wave band, which can resist path loss in the millimeter wave band. Moreover, compared with the classical MIMO-OFDM modulation, the MIMO-UFMC modulation proposed in the present application is based on a bit error rate (BER), a root-mean-square error (RMSE) of a soft estimated symbol, Gain is achieved in terms of throughput, showing the advantages of MIMO-UFMC modulation over MIMO-OFDM.

In one possible implementation, the signal

The at least two UFMC symbols are included, and a length of a guard interval between every two consecutive UFMC symbols in at least two UFMC symbols is less than or equal to a preset threshold. In this way, the GI is not used between adjacent UFMC symbols or a shorter GI is used, which can improve spectrum utilization.

In a possible implementation manner, the preset threshold is determined according to the filter length and the channel impulse response length in the UFMC modulation.

In a possible implementation manner, the method further includes: the transmitting end performs digital precoding on each subcarrier or subcarrier group corresponding to each UFMC symbol in the at least two UFMC symbols. Digital precoding, as part of hybrid precoding, can be combined with analog precoding to achieve complete beamforming precoding for optimal beamforming gain.

In a possible implementation manner, the coding matrix of the analog precoding is determined according to the result of the analog beamforming training; or the coding matrix of the analog precoding is determined according to the transmission beam number sent by the receiving end; or the analog precoding The coding matrix is determined based on the feedback information sent by the receiving end. In this way, when both the transmitting end and the receiving end have an analog beamforming training process, the transmitting end may perform beamforming training by using beam scanning, and the receiving end may transmit the beam number corresponding to the transmitting beam with the highest signal quality. Feedback to the sender.

In a possible implementation manner, the transmitting end performs general-purpose filtering multi-carrier UFMC modulation on at least one spatial stream or space-time stream to obtain a signal.

The method includes: the transmitting end performs parallel UFMC modulation on at least one spatial stream or space-time stream.

In a ninth aspect, the embodiment of the present application provides a sending apparatus, including: a modulating unit, configured to perform general-purpose filtering multi-carrier UFMC modulation on at least one spatial stream or space-time stream to obtain a signal.

Analog precoding unit for pairing signals

Perform analog precoding to get the signal

a sending unit for transmitting a signal to the receiving end

In one possible implementation, the signal

The at least two UFMC symbols are included, and a length of a guard interval between every two consecutive UFMC symbols in at least two UFMC symbols is less than or equal to a preset threshold.

In a possible implementation, the method further includes a digital precoding unit, configured to: at least two UFMC symbols

Each subcarrier or subcarrier group corresponding to each UFMC symbol in the number is digitally precoded.

In a possible implementation manner, the coding matrix of the analog precoding is determined according to the result of the analog beamforming training; or the coding matrix of the analog precoding is determined according to the transmission beam number sent by the receiving end; or the analog precoding The coding matrix is determined based on the feedback information sent by the receiving end.

In a possible implementation, the modulating unit is configured to perform parallel UFMC modulation on at least one spatial stream or space-time stream.

For technical effects of the ninth aspect and various alternative implementations, reference may be made to the technical effects of the eighth aspect and various alternative implementations thereof, and details are not described herein again.

In a tenth aspect, the embodiment of the present application provides a sending apparatus, including: a processor, configured to perform general-purpose filtering multi-carrier UFMC modulation on at least one spatial stream or space-time stream to obtain a signal.

The processor is also used to signal

Perform analog precoding to get the signal

Transmitter for transmitting signals to the receiver

In one possible implementation, the signal

In a possible implementation manner, the processor is further configured to perform digital precoding on each subcarrier or subcarrier group corresponding to each UFMC symbol in the at least two UFMC symbols.

In a possible implementation, the processor is configured to perform parallel UFMC modulation on at least one spatial stream or space-time stream.

In an eleventh aspect, an embodiment of the present application provides a device, which is in the form of a product of a chip. The device includes a processor and a memory, and the memory is coupled to the processor to save the necessary program of the device. The instructions and data are used by the processor to execute program instructions stored in the memory such that the apparatus performs the functions of the transmitting apparatus in the above method.

In a twelfth aspect, the embodiment of the present application provides a sending apparatus, which can implement the functions performed by the sending apparatus in the foregoing method embodiment, and the functions can be implemented by using hardware or by executing corresponding software by hardware. The hardware or software includes one or more modules corresponding to the above functions.

In one possible design, the structure of the transmitting device includes a processor and a communication interface configured to support the transmitting device to perform a corresponding function in the above method. The communication interface is used to support communication between the transmitting device and other network elements. The transmitting device can also include a memory for coupling with the processor that holds the program instructions and data necessary for the transmitting device.

In a thirteenth aspect, the embodiment of the present application provides a computer readable storage medium, comprising instructions, when executed on a computer, causing the computer to perform any one of the methods provided by the first aspect.

In a fourteenth aspect, the embodiment of the present application provides a computer program product comprising instructions, when executed on a computer, causing the computer to perform any one of the methods provided by the first aspect.

DRAWINGS

FIG. 1 is a schematic diagram of grouping subcarriers in a UFMC modulation process according to an embodiment of the present disclosure;

2 is a schematic structural diagram 1 of a communication system according to an embodiment of the present application;

FIG. 3 is a schematic structural diagram 2 of a communication system according to an embodiment of the present disclosure;

FIG. 4 is a schematic diagram of interaction between a signal sending and receiving method according to an embodiment of the present application;

FIG. 5 is a schematic structural diagram of a UFMC modulator according to an embodiment of the present disclosure;

FIG. 6 is a schematic diagram of a length of a GI between two consecutive UFMC symbols being less than a preset threshold according to an embodiment of the present disclosure;

FIG. 7 is a schematic diagram of a GI that is not set between two consecutive UFMC symbols according to an embodiment of the present disclosure;

FIG. 8 is a schematic diagram of performance comparison simulation of an MMSE and an MMSE-RC according to an embodiment of the present application; FIG.

FIG. 9 is a schematic diagram showing performance comparison between OFDM modulation and UFMC modulation provided by the embodiment of the present application;

FIG. 10 is a schematic diagram showing performance comparison between OFDM modulation and throughput of UFMC modulation provided by an embodiment of the present application;

FIG. 11 is a schematic structural diagram 1 of a receiving apparatus according to an embodiment of the present disclosure;

FIG. 12 is a schematic structural diagram 2 of a receiving apparatus according to an embodiment of the present disclosure;

FIG. 13 is a schematic structural diagram 1 of a sending apparatus according to an embodiment of the present disclosure;

FIG. 14 is a schematic structural diagram 2 of a transmitting apparatus according to an embodiment of the present application.

detailed description

For a clear and concise description of the following embodiments, a brief introduction of related concepts or techniques is first given:

Single-user MIMO (SU-MIMO): A plurality of parallel data streams occupying the same time-frequency resource are sent to the same user equipment or sent from the same user equipment to the base station.

The serial-to-parallel conversion divides a stream of information into multiple signals for simultaneous transmission.

FFT: A fast algorithm of discrete Fourier transform that converts a signal from the time domain to the frequency domain.

Antenna array: In the millimeter wave band, a transmit chain and a receive chain generally correspond to an antenna array. An antenna array is usually composed of multiple antenna elements, which are shaped by analog beams. Increase the antenna gain. For the sake of brevity, the present application simply refers to an antenna array as an antenna. In the present application, one antenna corresponds to one antenna port, and one antenna port corresponds to one or more antenna elements.

Spatial stream: One or more bitstreams or modulation symbol streams in multiple spatial dimensions generated by multiple antennas when both transceivers of a communication link use multiple antennas. A spatial stream can also be called a layer, and the number of spatial streams can be called a multiplexing order.

Space-time stream: A stream of modulation symbols generated after space-time processing of modulation symbols for one or more spatial streams. In general, one transmit antenna corresponds to at least one space-time stream.

The embodiment of the present application provides a signal sending and receiving method and device, which can be applied to a communication system using UFMC modulation and MIMO. For example, it can be applied to a Wireless Local Area Network (WLAN) or a cellular network using UFMC modulation and SU-MIMO on the millimeter wave band, which is suitable for uplink and/or downlink communication.

FIG. 2 is a schematic structural diagram 1 of a signal processing system according to an embodiment of the present application. The signal processing system includes a transmitting end and a receiving end. For example, the transmitting end may be a MIMO radio frequency (RF) transmitter, and the receiving end may be a MIMO RF receiver. Alternatively, the sender and receiver can be integrated into a MIMO RF transceiver. The transmitting end includes a UFMC module (UFMC modulator) and an analog precoding module. Further, the sender may further include a serial/parallel conversion (S/P) module and a digital precoding module. The receiving end includes an FFT module and an adaptive algorithm module. Further, the receiving end may further include parallel and serial conversion

(parallel/serial conversion, P/S) module and analog decoding module. among them:

The serial-to-parallel conversion module is configured to convert the serial to-be-transmitted signal into parallel M spatial streams, and M is an integer greater than or equal to 1.

Digital precoding module: used to convert M spatial streams into at least one space-time stream.

UFMC module: used to perform UFMC modulation on at least one space-time stream to obtain a signal

Analog precoding module: for signal pairing

Perform analog precoding to get the signal

Analog decoding module: used for analog decoding of the first UFMC signal Y _BB , signal Y _BB corresponding signal

FFT module; for corresponding to the receiving end

Each of the receiving antennas performs an N-point FFT on the C sampling points included in the first UFMC signal to obtain a second UFMC signal Z _BB .

Adaptive algorithm module: used to

Each of the receiving antennas selects J sampling points among the D sampling points included in the second UFMC signal, and obtains a third UFMC signal Z _BB,n , D is greater than C, and J is a positive integer smaller than D; Calculating the estimated value of the transmitted signal by calculating the third UFMC signal based on the adaptive algorithm

Parallel string conversion module: used to

Converted to a serial pending signal.

FIG. 3 is a schematic structural diagram 2 of a signal processing system provided by an embodiment of the present application. Different from FIG. 2, the receiving end may include an FFT module, a digital encoding module, and a frequency domain equalization (FDE) module. among them:

The digital encoding module can be used for baseband decoding (ie, digital decoding) of the first UFMC signal Y _BB ;

The FDE module can be used to perform frequency domain equalization on signals obtained after baseband decoding.

In the present application, the vector/matrix is represented by a bolded formal letter, and the scalar is represented by a non-bold italic/normal body.

The technical solutions in the embodiments of the present application will be described below with reference to the accompanying drawings in the embodiments of the present application. In the description of the present application, "partial" or "all" means one or more, and "multiple" means two or more than two unless otherwise stated. In addition, in order to facilitate the clear description of the technical solutions of the embodiments of the present application, in the embodiments of the present application, the words "first", "second", and the like are used to distinguish the same items or similar items whose functions and functions are substantially the same. Those skilled in the art can understand that the words "first", "second" and the like do not limit the number and execution order, and the words "first", "second" and the like are not necessarily limited.

The term "and/or" in this context is merely an association describing the associated object, indicating that there may be three relationships, for example, A and / or B, which may indicate that A exists separately, and both A and B exist, respectively. B these three situations. In addition, the character "/" in this article generally indicates that the contextual object is an "or" relationship; in the formula, the character "/" indicates that the contextual object is a "divide" relationship.

It should be noted that, in the embodiment of the present application, “of”, “corresponding, relevant” and “corresponding” may sometimes be mixed, and it should be noted that when the difference is not emphasized The meaning to be expressed is the same.

The embodiment of the present application provides a signal sending method, as shown in FIG. 4, including:

401. The transmitting end performs serial-to-parallel conversion on the serial to-be-transmitted signal.

For example, after the serial end-to-parallel conversion of the serial to-be-transmitted signal S ₀ of length (M×k), the transmitting end can obtain a matrix S of (M×k) dimensions, that is, S has M row vectors and k. Column vector. Wherein, the row vector of S includes S(1,:), S(2,:), ..., S(M,:). Each row vector S(m,:) is a vector of length k. Each data vector to be modulated of length k constitutes a spatial stream, and S includes a total of M spatial streams. Where k is the number of subcarriers of one UFMC symbol corresponding to each spatial stream in the subsequent UFMC modulation. M and k are integers greater than or equal to 1, m = 1, ..., M.

402. The transmitting end performs digital precoding on the M spatial streams to obtain at least one space-time stream.

S corresponding

One UFMC symbol of the antenna to be transmitted, when the transmitting end continuously transmits at least two UFMC symbols, the transmitting end may perform digital precoding on each subcarrier or subcarrier group corresponding to each UFMC symbol in at least two UFMC symbols. . That is, the transmitting end can perform digital precoding on the nth column vector S(:, n) of S. Where S(:, n) represents a signal that M spatial streams are loaded on subcarrier n.

Suppose that an encoder that performs digital precoding on S(:, n) is represented by a matrix as

The Q _BB (n) of the dimension, the nth column vector X(:,n)=Q _BB (n)S(:,n) of the output signal X of the digital precoder. Where X is

Dimensional space-time stream signal, ie X contains

A free time stream.

Indicates the number of transmitting antennas (transmitting RF chains) at the transmitting end, and each transmitting antenna corresponds to an antenna array including multiple antenna elements.

403. The transmitting end performs UFMC modulation on at least one spatial stream or space-time stream to obtain a signal.

In one possible design, the transmitting end can perform parallel UFMC modulation on at least one spatial stream or space-time stream.

In this embodiment, the UFMC modulation of at least one space-time stream X by the transmitting end is taken as an example for description. Specifically, the transmitting end can feed each row vector of X (corresponding to a space-time stream) into a UFMC modulator. As shown in FIG. 5, it is a schematic structural diagram of a UFMC modulator. The UFMC modulator may include a serial to parallel conversion module, a plurality of IFFT conversion modules in parallel, and a plurality of FIR filters in parallel. Each UFMC modulator may perform subcarrier grouping on an input signal input to the UFMC modulator, for example, grouping adjacent U subcarriers into one group, and may be divided into B subcarrier groups, where k=BU. Then, the B subcarrier groups are respectively subjected to IFFT transform, and respectively filtered by parallel B filters to obtain an output signal matrix.

It can be expressed as:

Dimension is

L is the length of the filter.

Each row vector can represent a UFMC symbol (also known as a UFMC block or UFMC packet).

The first line of the transposed matrix is expressed as:

Where G _i is a matrix of [(k+L-1)×k] dimensions for describing the discrete convolution operation of the filter g _i . g _i denotes the FIR filter for the ith sub-band, the internal elements of which are expressed as:

among them,

Is the normalized frequency shift of the i-th sub-band corresponding filter, and L is the length of the filter.

W _{k, IFFT} is a matrix of (k × k) dimensions, used to represent an isometric IFFT transform, the (a, b)th element is

a and b represent the rows and columns of W _{k, IFFT} , respectively.

P _i is a matrix of (k × k) dimensions, expressed as follows:

Wherein P _i represents the subcarrier of the (i+1)th subband is selected for subsequent FFT transform and FIR filtering, and diag() represents constructing a diagonal matrix according to the main diagonal vector.

In one possible design, the length of the guard interval (GI) between each successive two UFMC symbols in at least two UFMC symbols is less than or equal to a preset threshold. The preset threshold may be determined according to a filter length and a channel impulse response length in UFMC modulation. As shown in FIG. 6, the preset threshold may be (L+L _ch −2), and the GI length between two UFMC symbols adjacent to each other may be (L-1), and (L-1) is smaller than (L+). L _ch –2). It can be seen from Fig. 6 that no interference occurs between UFMC symbols, and the filtered UFMC symbol generates interference, and the UFMC symbol transmitted to the receiving end generates more serious interference. This interference can be eliminated by an adaptive algorithm (e.g., MMSE algorithm) used in subsequent steps of embodiments of the present application. Where (L+L _ch –2) can represent the amount of extension of each space-time stream signal caused by UFMC modulation and channel-induced filter effects, L represents the filter length in UFMC modulation, and L _ch represents the channel impulse response. length.

In one possible design, no guard interval may be set between every two consecutive UFMC symbols in at least two UFMC symbols. As shown in FIG. 7, the GI length between two adjacent UFMC blocks transmitted by the transmitting end is 0.

In this way, the GI is not used between adjacent UFMC symbols or a shorter GI is used, which can improve spectrum utilization.

404, the sender pair signal

(Signal obtained after UFMC modulation) is subjected to analog precoding to obtain a signal

The transmitting end can shape the code pair according to the analog beam

Each column vector in all column vectors is separately subjected to analog beam precoding to obtain (N _T ×1)-dimensional signals.

The analog precoding can be analog beamforming coding. N _T represents the total number of antenna elements of all transmit antennas.

The coding matrix of the analog precoding is determined according to the result of the simulation beamforming training; or the coding matrix of the analog precoding is determined according to the transmission beam number sent by the receiving end; or the coding matrix of the analog precoding is transmitted according to the receiving end Feedback information is determined. It should be noted that when the UFMC signal is transmitted in the millimeter wave band, the analog beamforming precoding can improve the antenna gain, increase the link budget, and achieve beam alignment between the transmitting device and the receiving device.

Exemplarily, the coding matrix of the analog beamforming coding may be Q _RF , and the dimension is

N _T represents the total number of transmit elements included in all transmit antennas. Q _RF can be obtained according to the correlation method of Q ^opt (n) matrix decomposition, and Q ^opt (n) represents the optimal precoding of the nth column (ie, the nth subcarrier of the UFMC symbol) of the transmission signal S to be transmitted by the transmitting end. The matrix Q ^opt (n) contains and

The largest number of singular values associated with

M column. among them,

It is obtained by performing singular value decomposition (SVD) decomposition on the frequency domain channel coefficient H(2n). among them,

with

Representation

A matrix composed of eigenvectors after singular value decomposition. In addition, Q _BB (n) can also be obtained by the correlation method of Q ^opt (n) and matrix decomposition.

In one possible design, according to Q ^opt = Q _RF Q _BB, solve the following optimization problem Q _RF:

For example, the solution of the above optimization problem can be obtained by applying a Block Coordinate Descent for Subspace Decomposition (BCD-SD) algorithm. Where arg min represents the value of the variable when the subsequent expression reaches the minimum value, || || _F represents the Frobenius norm, || represents the absolute value of the variable, c and d Represents the row and column of Q _RF , * represents the estimated value of the corresponding variable sought, and kM represents the estimated value of the variable.

405. The transmitting end sends, by using multiple antennas, a signal that performs UFMC modulation and analog precoding to the receiving end.

That is, the sender passes

Transmitting antennas send signals to the receiving end

406, the receiving end passes

The receiving antennas receive the first UFMC signal Y _BB .

First UFMC signal Y _BB and transmitted signal

Correspondingly, the receiving end can receive the signal Y _BB through a plurality of receiving antennas.

The receiving end may include an analog decoding module, and the analog decoding may also be referred to as an analog beamforming encoding at the receiving end, which can perform analog decoding on the signal Y _BB . In a possible design, the receiving end may send an analog precoding coding matrix or beam number to the transmitting end, and the coding matrix is determined according to the result of the analog beamforming training; or the receiving end sends the analog precoding to the transmitting end. The coding matrix and the digital precoding matrix.

Exemplarily, the analog beamforming coding matrix corresponding to the receiver may be D _RF , and the D _RF dimension may be

D _RF can be obtained based on beamforming training of both parties. For example, D ^opt (n) can be computed according to the related method of matrix decomposition. D ^opt (n) represents the analog beamforming coding matrix of the nth column of the matrix S, and the matrix D ^opt (n) contains and

The largest number of singular values associated with

M column. among them,

Is obtained by performing singular value decomposition on the frequency domain channel coefficient H(2n),

In another possible design, the D _RF can obtain the optimal precoding matrix D ^opt according to the channel state information obtained by the receiving end according to the measurement, and then obtain the following optimization problem according to D ^opt = D _RF D _BB to obtain the following optimization problem:

The solution to the above optimization problem can be obtained by applying the BCD-SD algorithm. Where arg min represents the value of the variable when the subsequent expression reaches the minimum value, || || _F represents the Frobenius norm, | | represents the absolute value of the variable, and c and d represent the D _RF Rows and columns, * indicates the estimated value of the corresponding variable.

When the Power Amplifier (PA) nonlinearity is neglected, the output of the M-dimensional vector (ie, M spatial streams) transmitted at time n is simulated beamformed and encoded as follows:

Where P _T represents the transmit power,

Indicates the channel impulse response of the (N _R ×N _T ) dimension, L represents the dimension of the prototype filter (filter response length), n represents the time, l represents the sequence number in the convolution operation, and L _ch is the channel impulse response length The representation (in discrete samples), the dimension of Y _BB is [N _R ^RF ×(k+L+L _ch -2)], and w(n) represents additive thermal noise. The operator H represents a Hermitian transpose.

407, receiving end pair

Each of the receiving antennas performs N-point FFT on the C sampling points included in the first UFMC signal to obtain a second UFMC signal Z _BB .

Where C is an integer greater than k, N is an integer greater than k, and C is less than or equal to N. For example, C=k+L+L _ch –2. Alternatively, the last S sample points (column vectors) of Y _BB may be discarded before the FFT is performed, S=(L+L _ch −2),

Dimensional

Target again

Perform an FFT transformation.

Exemplarily, the receiving end can be

Each column vector performs a 2k point FFT transform to obtain a second UFMC signal Z _BB , Z _BB as follows:

Z _BB = Y _BB W _{2k, FFT} (1: k + L + L _ch -2, :)

Among them, the matrix W _{2k, FFT} represents an FFT transform of 2k points, W _{2k, and FFT} is a (2k×2k) dimension. Z _BB is (N _R ^RF × D) dimension. For example, D=2k+L+L _ch –2. Alternatively, the rear (L+L _ch –2) symbols of Z _BB can be discarded, ie D=2k.

Optional, the receiving end can be

The output after the 2k point FFT transform is subjected to 2 times downsampling.

After simulation evaluation,

Performing a 2k point FFT can reduce the computational overhead of the receiver because it can concentrate the contribution of the subcarrier signal on a subset of pre-acknowledged subcarriers, thereby obtaining signal estimates for all subcarriers corresponding to the transmitted signal.

408, the receiving end from

Each of the receiving antennas selects J sampling points among the D sampling points included in the second UFMC signal to obtain a third UFMC signal Z _BB,n , D is greater than C, and J is a positive integer smaller than D.

When n==1, I _min,1 =1, I _max,1 =J-2, I _min,2 =2k-1, I _max,2 =2k

When n==k, I _min,1 =1, I _max,1 =2, I _min,2 =2k-J+3, I _max,2 =2k

The third UFMC signal Z _{BB,n is} as follows:

Z _BB,n =[Z _BB (:,I _min,1 :I _max,1 ),Z _BB (:,I _min,2 :I _max,2 )]

when

And

Time,

when

When I _min =1, I _max =J;

when

When I _min = 2k-J+1, I _max = 2k;

The third UFMC signal Z _{BB,n is} as follows:

Indicates the range of sample points that J sample points include in D sample points. The operator "==" means constant.

The present application uses a data window of dimension (N _R ^RF × J), that is, a matrix Z _{BB,n of} (N _R ^RF ×J) dimension can be used to represent the estimation of the transmitted signal on the nth subcarrier by the receiving end, n =1,...,k. Compared with the prior art, the calculation cost of obtaining the estimated value of the signal on all subcarriers by the traditional MMSE algorithm is the order of the cube of the number of subcarriers k. The simplified MMSE method provided by the embodiment of the present application (MMSE- RC) The required computational complexity is

Cube. It can be seen that the complexity of the equalization algorithm proposed in the embodiment of the present application is significantly reduced. For example, it is assumed that the Dolph-Chebyshev filter is used in the UFMC modulation provided by the embodiment of the present application, and the length is L=16, the number of subcarriers is k=128, and the number of subbands is B. = 8, the number of subcarriers in each subband U = 16; each data symbol uses 4-QAM modulation, where QAM represents quadrature amplitude modulation; antenna configuration is N _R × N _T = 16 ×64, and

Where N _T represents the total number of transmit array elements included in all transmit antennas, and N _R represents the total number of receive array elements included in all receive antennas. As shown in FIG. 8, the performance comparison simulation diagram of MMSE and MMSE-RC under the above conditions is shown. Line a in Figure 8 represents UFMC-mmse, G, CI, line b represents UFMC-mmse-RC, G, CI, line c represents UFMC-mmse, NG, CI, and line d represents UFMC-mmse-RC, NG, CI, line e represents UFMC-mmse, G, CD, line f represents UFMC-mmse-RC, G, CD, line g represents UFMC-mmse, NG, CD, and line h represents UFMC-mmse-RC, NG, CD. Where G indicates that there is a GI between adjacent UFMC symbols, NG indicates that there is no GI between adjacent UFMC symbols, CI indicates that UFMC modulation is channel dependent, and CD indicates that UFMC modulation is channel independent. It can be seen that the throughput of the MMSE-RC equalization algorithm proposed in the embodiments of the present application is greatly improved compared with the traditional MMSE algorithm under various conditions.

409. The receiving end performs an operation on the third UFMC signal based on an adaptive algorithm to obtain an estimated value of the transmitted signal.

The adaptive algorithm may include a minimum mean square error MMSE algorithm, an NLMS algorithm or an RLS algorithm.

In the following, the receiver performs an operation on the third UFMC signal based on the MMSE algorithm to obtain an estimated value of the transmitted signal.

Give an example for explanation. Specifically, the receiving end may determine the estimated value of the transmitted signal according to the vectorized signal z _{BB,n of the} third signal Z _BB, _n and the first parameter d _RC (n)

Where z _BB,n =vec(Z _BB,n ), z _BB,n denotes that all columns of Z _BB,n are sequentially connected into one column.

As follows:

The first parameter d _RC (n) is as follows:

When n==1, I _min,1 =1, I _max,1 =J-2, I _min,2 =2k-1, I _max,2 =2k

When n==k, I _min,1 =1, I _max,1 =2, I _min,2 =2k-J+3, I _max,2 =2k

when And

Time,

when

When I _min =1, I _max =J;

when

When I _min = 2k-J+1, I _max = 2k;

among them,

Represents the number of samples used to calculate the time average,

more than the

S _l (:, n) represents the value of the transmitted signal at the nth time.

Compared with the prior art, the calculation overhead of obtaining the estimated value of the signal on all subcarriers by the conventional MMSE algorithm is on the order of the cube of the number k of subcarriers, and the signal receiving method provided by the embodiment of the present application provides a simplified The MMSE scheme makes the computational complexity of obtaining the estimated values of the signals on all subcarriers only

In addition, in the embodiment of the present application, the receiving end uses the linear MMSE or the simplified complexity MMSE algorithm to equalize and detect the MIMO-UFMC signal (for example, the first UFMC signal), which can reduce the inter-block interference of the MIMO-UFMC signal.

In one possible design, steps 407-409 may be replaced with step 410.

410. The first UFMC signal Y _BB at the receiving end performs digital decoding to obtain a decoded signal.

In one possible design, the receiving end can perform an equal-sized 2k-point FFT transform on each column vector of Y _BB and then down-sample the FFT output by 2 times. Then, the downsampled output is digitally decoded, and the decoded signal is as follows:

The approximate sign in the above equation is because the UFMC usually discards the last L _ch -1 symbols.

The 2nth coefficient of the 2k point FFT of the filter g _i representing the i-th sub-band, i=n/d.

D _BB (n),

The operation of D ^opt (n) can be obtained by a related method of matrix decomposition. For the specific process, reference may be made to step 406. Q _RF and Q _BB (n) can be obtained by the related methods of Q ^opt (n) and matrix decomposition. For the specific process, reference may be made to step 404.

The estimated value of the transmitted signal at the receiving end at time n is:

Among them, "+" means the Moore-Penrose generalized inverse matrix.

signal

It can be sent to the receiving end through multiple transmitting antennas on the transmitting end, and the MIMO-UFMC signal can be transmitted in the millimeter wave frequency band. Further, the signal transmission method adopts a MIMO-UFMC modulation method for the millimeter wave band, which can resist the path loss of the millimeter wave band. For example, it is assumed that the Dolph Chebyshev filter is used in the UFMC modulation provided by the embodiment of the present application, and the length is L=16, the number of subcarriers is k=128, and the number of subbands B= 8, the number of subcarriers in each subband U = 16; each data symbol uses 4-QAM modulation; the antenna configuration is N _R × N _T = 16 × 64, and

Where N _T represents the total number of transmit array elements included in all transmit antennas, and N _R represents the total number of receive array elements included in all receive antennas. As shown in FIG. 9, the performance comparison between the OFDM modulation under the above conditions and the error rate of the UFMC modulation provided by the embodiment of the present application is shown. Line a in Fig. 9 represents UFMC-mmse, line b represents UFMC-no dis, line c represents UFMC-id, and line d represents OFDM modulation. Where no dis indicates that the tail symbol of the UFMC signal is not discarded, and UFMC-id indicates that according to the formula

Perform UFMC signal estimation. As shown in FIG. 10, a performance comparison diagram of the throughput of the OFDM modulation and the UFMC modulation provided by the embodiment of the present application is performed. Line a in Fig. 10 represents OFDM modulation, line b represents UFMC mmse MP-G FD, line c represents UFMC-no dis FD, and line d represents UFMC mmse MP-NG FD. Wherein, FD indicates that the UFMC symbol is digitally encoded, and MP indicates that the UFMC signal includes a plurality of UFMC symbols. It can be seen that compared with the classical OFDM modulation, the MIMO-UFMC modulation proposed by the present application obtains gains in terms of bit error rate and throughput, and shows the feasibility of MIMO-UFMC modulation and the performance advantages compared with MIMO-OFDM.

The embodiment of the present application provides a signal receiving method, where the receiving end can receive the first UFMC signal Y _BB through multiple receiving antennas, where the first signal is a UFMC-MIMO signal sent by the transmitting end, and the first UFMC signal Y _BB includes The multipath effect, that is, the superposition of amplitude and phase changes, requires cancellation to restore the original signal at the transmitting end. The receiving end may obtain an estimated value of the transmitted signal on the basis of reducing the number of sampling points included in the UFMC signal.

Estimated value of the transmitted signal

It refers to the signal that the receiving end restores the transmitted signal with multipath effect. Therefore, the signal receiving method provided by the embodiment of the present application can be used for receiving the MIMO-UFMC signal in the millimeter wave band. It should be noted that the estimated value of the transmitted signal can be calculated based on the adaptive algorithm by reducing the number of sampling points included in the UFMC signal.

The solution provided by the embodiment of the present application is mainly introduced from the perspectives of the transmitting end and the receiving end (the transmitting device and the receiving device). It can be understood that, in order to implement the above functions, the transmitting end and the receiving end include corresponding hardware structures and/or software modules for performing respective functions. Those skilled in the art will readily appreciate that the present application can be implemented in a combination of hardware or hardware and computer software in conjunction with the algorithm steps described in the embodiments disclosed herein. Whether a function is implemented in hardware or computer software to drive hardware depends on the specific application and design constraints of the solution. A person skilled in the art can use different methods to implement the described functions for each particular application, but such implementation should not be considered to be beyond the scope of the present application.

The embodiment of the present application may divide the function module by the sending end and the receiving end according to the foregoing method example. For example, each function module may be divided according to each function, or two or more functions may be integrated into one processing module. The above integrated modules can be implemented in the form of hardware or in the form of software functional modules. It should be noted that the division of the module in the embodiment of the present application is schematic, and is only a logical function division, and the actual implementation may have another division manner.

FIG. 11 is a schematic diagram showing a possible structure of the receiving apparatus 11 involved in the foregoing embodiment, and the receiving apparatus includes: a receiving unit 1101, a processing unit 1102, and a transmitting unit. 1103. The receiving unit 1101 is configured to support the transmitting device to perform the process 406 in FIG. 4; the processing unit 1102 is configured to support the transmitting device to perform the processes 407-409 in FIG. All the related content of the steps involved in the foregoing method embodiments may be referred to the functional descriptions of the corresponding functional modules, and details are not described herein again.

In the case of employing an integrated unit, FIG. 12 shows a possible structural diagram of the receiving apparatus involved in the above embodiment. The receiving device 12 includes a processor 1201, a transceiver 1202, a memory 1203, and a bus 1204. The transceiver 1202, the processor 1201, and the memory 1203 are connected to each other through a bus 1204. The bus 1204 may be a Peripheral Component Interconnect (PCI) bus or an Extended Industry Standard Architecture (EISA) bus. Wait. The bus can be divided into an address bus, a data bus, a control bus, and the like. For ease of representation, only one thick line is shown in Figure 12, but it does not mean that there is only one bus or one type of bus.

FIG. 13 is a schematic diagram showing a possible configuration of the transmitting apparatus 13 involved in the foregoing embodiment. The transmitting apparatus includes: a modulating unit 1301 and an analog pre-encoding unit 1302. The transmitting unit 1303 and the digital pre-encoding unit 1304. The modulating unit 1301 is configured to support the transmitting device to perform the process 403 in FIG. 4; the analog pre-encoding unit 1302 is configured to support the transmitting device to perform the process 404 in FIG. 4; the transmitting unit 1303 is configured to support the transmitting device to perform the process 405 in FIG. 4; Digital precoding unit 1304 is operative to support the transmitting device to perform process 402 in FIG. Modulation unit 1301, analog precoding unit 1302. All the related content of the steps involved in the foregoing method embodiments may be referred to the functional descriptions of the corresponding functional modules, and details are not described herein again.

In the case of employing an integrated unit, FIG. 14 shows a possible structural diagram of the transmitting apparatus involved in the above embodiment. The transmitting device 14 includes a processor 1401, a transceiver 1402, a memory 1403, and a bus 1404. The transceiver 1402, the processor 1401, and the memory 1403 are mutually connected by a bus 1404; the bus 1404 may be a PCI bus or an EISA bus or the like. The bus can be divided into an address bus, a data bus, a control bus, and the like. For ease of representation, only one thick line is shown in Figure 14, but it does not mean that there is only one bus or one type of bus.

The steps of a method or algorithm described in connection with the present disclosure may be implemented in a hardware or may be implemented by a processor executing software instructions. The software instructions may be composed of corresponding software modules, which may be stored in a random access memory (RAM), a flash memory, a read only memory (ROM), an erasable programmable read only memory ( Erasable Programmable ROM (EPROM), electrically erasable programmable read only memory (EEPROM), registers, hard disk, removable hard disk, compact disk read only (CD-ROM) or any other form of storage medium known in the art. An exemplary storage medium is coupled to the processor to enable the processor to read information from, and write information to, the storage medium. Of course, the storage medium can also be an integral part of the processor. The processor and the storage medium can be located in an ASIC. Additionally, the ASIC can be located in a core network interface device. Of course, the processor and the storage medium may also exist as discrete components in the core network interface device.

Those skilled in the art will appreciate that in one or more examples described above, the functions described herein can be implemented in hardware, software, firmware, or any combination thereof. When implemented in software, the functions may be stored in a computer readable medium or transmitted as one or more instructions or code on a computer readable medium. Computer readable media includes both computer storage media and communication media including any medium that facilitates transfer of a computer program from one location to another. A storage medium may be any available media that can be accessed by a general purpose or special purpose computer.

The specific embodiments of the present invention have been described in detail with reference to the specific embodiments of the present application. It is to be understood that the foregoing description is only The scope of protection, any modifications, equivalent substitutions, improvements, etc. made on the basis of the technical solutions of the present application are included in the scope of protection of the present application.

Claims

A signal receiving method, comprising:

Receiving end
Receiving antennas receive a first general-purpose filtered multi-carrier UFMC signal Y BB ; wherein the first UFMC signal includes at least one UFMC symbol, and each UFMC symbol includes k sub-carriers,
And k is an integer greater than or equal to 1;

The receiving end is configured to
Each of the receiving antennas performs N-point fast Fourier transform FFT on the C sampling points included in the first UFMC signal to obtain a second UFMC signal Z BB , where C is an integer greater than k, and N is greater than An integer of k, C is less than or equal to N;

The receiving end from the
Each of the receiving antennas selects J sampling points among the D sampling points included in the second UFMC signal to obtain a third UFMC signal Z BB,n , D is greater than C, and J is a positive integer smaller than D;

The receiving end performs an operation on the third UFMC signal based on an adaptive algorithm to obtain an estimated value of the transmitted signal.
The method of claim 1 wherein said receiving end is from said
Each of the receiving antennas selects J sampling points among the D sampling points included in the second UFMC signal to obtain a third UFMC signal Z BB, n includes:

when
And
Time,

when
When I min =1, I max =J;

when
When I min = 2k-J+1, I max = 2k;

The third UFMC signal Z BB,n is as follows:

, N represents the sample points D at any one sampling point of the serial number, I min represents a lower limit of the sampling point of the reception end determines the Z BB, I max represents the upper limit of the sampling point of the reception end determines the Z BB,

Representing a range of sample points included in the D sample points by the J sample points.
The method according to claim 2, wherein the receiving end calculates the estimated value of the transmitted signal by calculating the third UFMC signal based on an adaptive algorithm, including:

The receiving end determines an estimated value of the transmitted signal according to the vectorized signal z BB,n of the third signal Z BB,n and the first parameter d RC (n)
As follows:

The first parameter d RC (n) is as follows:

among them,
Indicates the number of samples used to calculate the time average, S 1 (:, n) represents the value of the transmitted signal at the nth time, and H represents the conjugate transpose operator.
The method according to any one of claims 1-3, wherein the adaptive algorithm comprises a minimum mean square error MMSE algorithm, a normalized least mean square NLMS algorithm or a recursive least mean square RLS algorithm.
The method according to any one of claims 1 to 4, wherein said receiving end pairs said
Before each of the receiving antennas performs the N-point fast Fourier transform FFT to obtain the second UFMC signal Z BB in the C sampling points included in the first UFMC signal, the method further includes:

The receiving end discards the last S sample points of the first UFMC signal; wherein S is determined according to a length parameter of the filter and/or a length parameter of the channel impulse response when the UFMC signal is modulated.
The method according to any one of claims 1 to 5, wherein the receiving end passes
Before the receiving antenna receives the first general-purpose filtered multi-carrier UFMC signal Y BB , the method further includes:

Transmitting, by the receiving end, an analog precoding coding matrix or a beam number to the transmitting end, where the coding matrix is determined according to a result of the simulated beamforming training;

Alternatively, the receiving end sends an analog precoding coding matrix and a digital precoding matrix to the transmitting end.
A signal transmitting method, characterized in that

The transmitting end performs general-purpose filtering on at least one spatial stream or space-time stream to obtain a signal by multi-carrier UFMC modulation.
The transmitting end pairs the signal
Perform analog precoding to get the signal

The transmitting end sends the signal to the receiving end
The method of claim 7 wherein:

The signal
The at least two UFMC symbols are included, and a length of a guard interval between every two consecutive UFMC symbols in the at least two UFMC symbols is less than or equal to a preset threshold.
The method of claim 8 wherein said predetermined threshold is determined based on a filter length and a channel impulse response length in UFMC modulation.
The method according to claim 8 or 9, wherein the method further comprises:

The transmitting end performs digital precoding on each subcarrier or subcarrier group corresponding to each UFMC symbol in the at least two UFMC symbols.
A method according to any one of claims 7 to 10, wherein

The analog precoded coding matrix is determined based on the results of the simulated beamforming training; or

The analog precoding coding matrix is determined according to a transmit beam number sent by the receiving end; or

The coding matrix of the analog precoding is determined according to the feedback information sent by the receiving end.
The method according to any one of claims 7 to 11, wherein the transmitting end performs general-purpose filtering multi-carrier UFMC modulation on at least one spatial stream or space-time stream to obtain a signal.
include:

The transmitting end performs parallel UFMC modulation on the at least one spatial stream or space-time stream.
A receiving device, comprising:

Receiving unit for passing
Receiving antennas receive a first general-purpose filtered multi-carrier UFMC signal Y BB ; wherein the first UFMC signal includes at least one UFMC symbol, and each UFMC symbol includes k sub-carriers,
And k is an integer greater than or equal to 1;

a processing unit for
Each of the receiving antennas performs N-point fast Fourier transform FFT on the C sampling points included in the first UFMC signal to obtain a second UFMC signal Z BB , where C is an integer greater than k, and N is greater than An integer of k, C is less than or equal to N;

The processing unit is further configured to
Each of the receiving antennas selects J sampling points among the D sampling points included in the second UFMC signal to obtain a third UFMC signal Z BB,n , D is greater than C, and J is a positive integer smaller than D;

The processing unit is further configured to calculate the estimated value of the transmitted signal by calculating the third UFMC signal based on an adaptive algorithm.
The receiving device according to claim 13, wherein

when
And
Time,

when
When I min =1, I max =J;

when
When I min = 2k-J+1, I max = 2k;

The third UFMC signal Z BB,n is as follows:

, N represents the sample points D at any one sampling point of the serial number, I min represents a lower limit of the sampling point of the reception end determines the Z BB, I max represents the upper limit of the sampling point of the reception end determines the Z BB,

Representing a range of sample points included in the D sample points by the J sample points.
The receiving device according to claim 14, wherein the processing unit is configured to:

Determining an estimated value of the transmitted signal based on the vectorized signal z BB,n of the third signal Z BB,n and the first parameter d RC (n)
As follows:

The first parameter d RC (n) is as follows:

among them,
Indicates the number of samples used to calculate the time average, S 1 (:, n) represents the value of the transmitted signal at the nth time, and H represents the conjugate transpose operator.
The receiving apparatus according to any one of claims 13-15, wherein the adaptive algorithm comprises a minimum mean square error MMSE algorithm, a normalized least mean square NLMS algorithm or a recursive least mean square RLS algorithm.
The receiving device according to any one of claims 13 to 16, wherein the processing unit is configured to
Before each of the receiving antennas performs the N-point fast Fourier transform FFT to obtain the second UFMC signal Z BB in the C sampling points included in the first UFMC signal, the processing unit is further configured to:

Discarding the last S sample points of the first UFMC signal; wherein S is determined according to a length parameter of the filter and/or a length parameter of the channel impulse response when the UFMC signal is modulated.
The receiving device according to any one of claims 13-17, further comprising a transmitting unit, configured to:

Transmitting an analog precoded coding matrix or beam number to the transmitting end, the coding matrix being determined according to a result of the simulated beamforming training;

Alternatively, an analog precoding coding matrix and a digital precoding matrix are transmitted to the transmitting end.
A transmitting device, comprising:

a modulating unit configured to perform general-purpose filtering on at least one spatial stream or space-time stream to obtain a signal by multi-carrier UFMC modulation

An analog precoding unit for the signal
Perform analog precoding to get the signal

a sending unit, configured to send the signal to the receiving end
The transmitting device according to claim 19, characterized in that

The signal
The at least two UFMC symbols are included, and a length of a guard interval between every two consecutive UFMC symbols in the at least two UFMC symbols is less than or equal to a preset threshold.
The transmitting apparatus according to claim 20, wherein said preset threshold is determined according to a filter length and a channel impulse response length in UFMC modulation.
The transmitting device according to claim 20 or 21, further comprising a digital precoding unit, configured to:

Performing digital precoding on each subcarrier or subcarrier group corresponding to each of the at least two UFMC symbols.
A transmitting apparatus according to any one of claims 19 to 22, characterized in that

The analog precoded coding matrix is determined based on the results of the simulated beamforming training; or

The analog precoding coding matrix is determined according to a transmit beam number sent by the receiving end; or

The coding matrix of the analog precoding is determined according to the feedback information sent by the receiving end.
The transmitting device according to any one of claims 19 to 23, wherein the modulating unit is configured to:

Parallel UFMC modulation is performed on the at least one spatial stream or space-time stream.