WO2019080026A1 - 非正交解调模块、触控系统及非正交解调方法 - Google Patents

非正交解调模块、触控系统及非正交解调方法

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Publication number
WO2019080026A1
WO2019080026A1 PCT/CN2017/107757 CN2017107757W WO2019080026A1 WO 2019080026 A1 WO2019080026 A1 WO 2019080026A1 CN 2017107757 W CN2017107757 W CN 2017107757W WO 2019080026 A1 WO2019080026 A1 WO 2019080026A1
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WIPO (PCT)
Prior art keywords
orthogonal
frequency
phase
corrected
frequencies
Prior art date
Application number
PCT/CN2017/107757
Other languages
English (en)
French (fr)
Inventor
周欣瑞
文亚南
梁颖思
Original Assignee
深圳市汇顶科技股份有限公司
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Publication date
Application filed by 深圳市汇顶科技股份有限公司 filed Critical 深圳市汇顶科技股份有限公司
Priority to PCT/CN2017/107757 priority Critical patent/WO2019080026A1/zh
Priority to CN201780001414.8A priority patent/CN107980114B/zh
Priority to EP17909664.9A priority patent/EP3502854B1/en
Priority to US16/195,786 priority patent/US10852878B2/en
Publication of WO2019080026A1 publication Critical patent/WO2019080026A1/zh

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    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
    • G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
    • G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
    • G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
    • G06F3/0416—Control or interface arrangements specially adapted for digitisers
    • G06F3/04166—Details of scanning methods, e.g. sampling time, grouping of sub areas or time sharing with display driving
    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
    • G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
    • G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
    • G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
    • G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
    • G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
    • G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
    • G06F3/0416—Control or interface arrangements specially adapted for digitisers
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/22—Demodulator circuits; Receiver circuits
    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
    • G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
    • G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
    • G06F3/041—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means
    • G06F3/044—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means by capacitive means
    • G06F3/0446—Digitisers, e.g. for touch screens or touch pads, characterised by the transducing means by capacitive means using a grid-like structure of electrodes in at least two directions, e.g. using row and column electrodes
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K9/00—Demodulating pulses which have been modulated with a continuously-variable signal
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/10—Frequency-modulated carrier systems, i.e. using frequency-shift keying
    • H04L27/14—Demodulator circuits; Receiver circuits
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/22—Demodulator circuits; Receiver circuits
    • H04L27/233—Demodulator circuits; Receiver circuits using non-coherent demodulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/38—Demodulator circuits; Receiver circuits
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/38—Demodulator circuits; Receiver circuits
    • H04L27/3845—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier

Definitions

  • the present invention relates to a non-orthogonal demodulation module, a touch system and a non-orthogonal demodulation method, and more particularly to a non-quadrature demodulation module, a touch system and a non-orthogonal demodulation method for reducing signal bandwidth.
  • the operational interfaces of various electronic products have gradually become more humanized in recent years.
  • the user can directly operate on the screen with a finger or a stylus, input information/text/pattern, and save the trouble of using an input device such as a keyboard or a button.
  • the touch screen usually consists of a sensing panel and a display disposed behind the sensing panel.
  • the electronic device judges the meaning of the touch according to the position touched by the user on the sensing panel and the picture presented by the display at the time, and executes the corresponding operation result.
  • the existing touch technology has been developed to simultaneously (at the same time) use two different frequencies and mutually orthogonal signals to code the two transmission electrodes of the touch system (ie, transmit two signals to two electrodes) due to
  • the coded signals are orthogonal to one another and the signals carried by the different frequencies can be resolved during the demodulation process.
  • the two mutually orthogonal signal spectra shown in FIG. 6 have frequencies f a and f b , respectively, and the signal frequencies corresponding to the two mutually orthogonal signals are required to maintain a specific frequency interval with each other in order to maintain their mutually orthogonal characteristics.
  • the signal bandwidth the bandwidth occupied by the signals
  • the signal bandwidth is large, and it is necessary to ensure that there is no other interference in the signal bandwidth, and the difficulty in designing the touch system is increased.
  • some embodiments of the present application aim to provide a non-orthogonal demodulation module, a touch system, and a non-orthogonal demodulation method that reduce signal bandwidth to improve the disadvantages of the prior art.
  • the embodiment of the present application provides a non-orthogonal demodulation module that demodulates a received signal.
  • the received signal is related to a sum of a plurality of transmission signals corresponding to a plurality of frequencies, the plurality of transmission signals are non-orthogonal to each other, and the non-orthogonal demodulation module includes a mixing integration unit And performing, respectively, mixing and integrating the received signals on the plurality of frequencies to generate a plurality of in-phase components and a plurality of orthogonal components corresponding to the plurality of frequencies; and decoding units for generating At least one decoding matrix, and calculating a plurality of energy corresponding to the plurality of transmitted signals according to the at least one decoding matrix, the plurality of in-phase components, and the plurality of orthogonal components.
  • the decoding unit is configured to perform the steps of: arranging the plurality of in-phase components into an in-phase vector, and arranging the plurality of orthogonal components (Quadrature Component) into an orthogonal vector; Obtaining at least one matrix, wherein the at least one matrix has a plurality of non-diagonal terms, the plurality of non-diagonal terms being related to at least one frequency difference, the at least one frequency difference being two of the plurality of frequencies a difference of the at least one decoding matrix, the at least one decoding moment
  • the array is proportional to the inverse matrix of the at least one matrix; obtaining an in-phase result and an orthogonal result according to the at least one decoding matrix, the in-phase vector, and the orthogonal vector; and according to the in-phase result and the The orthogonal result calculates the plurality of energies that are to be applied to the plurality of transmitted signals.
  • the plurality of off-diagonal terms are related to the at least one frequency difference and the at least one frequency sum, and the at least one frequency sum is a sum of two of the plurality of frequencies.
  • the mixing integration unit applies a window function to the received signal, the window function corresponds to a window spectrum, and the plurality of non-diagonal terms are related to at least one difference spectral value, the at least one difference spectral value
  • the spectral value of the window corresponds to the spectral value of the at least one frequency difference.
  • the plurality of off-diagonal terms are related to the at least one difference spectrum value and the at least one sum spectrum value, and the at least one sum spectrum value corresponds to a spectrum value of the at least one frequency sum, At least one frequency and a sum of two of the plurality of frequencies.
  • the embodiment of the present application provides a touch system including a plurality of transmitting electrodes, a plurality of receiving electrodes, and a signal generating module coupled to the plurality of transmitting electrodes at a first time.
  • the signal generating module respectively transmits a plurality of transmission signals to the plurality of transmission electrodes, the plurality of transmission signals corresponding to a plurality of frequencies, the plurality of transmission signals being non-orthogonal to each other; and a non-orthogonal demodulation module
  • the non-orthogonal demodulation module receives a received signal of a first one of the plurality of receiving electrodes, the non-orthogonal solution is coupled to the plurality of transmitting electrodes.
  • the tuning module includes a mixing and integrating unit for separately mixing the received signals on the plurality of frequencies and Integrating to generate a plurality of in-phase components corresponding to the plurality of frequencies and a plurality of orthogonal components; and decoding units for generating at least one decoding matrix, and according to the at least one decoding matrix, the plurality of in-phase components And the plurality of orthogonal components, calculating a plurality of energies corresponding to the plurality of transmitted signals.
  • the signal generating module transmits a first transmission signal to a first one of the plurality of transmitting electrodes, and the non-orthogonal demodulation module is received by the first receiving electrode a correction signal, the mixing integration unit generating a plurality of corrected in-phase components corresponding to the plurality of frequencies and a plurality of corrected orthogonal components according to the correction signal, the decoding unit according to the plurality of corrected in-phase components or The correcting the quadrature component to generate the at least one matrix, the first transmit signal corresponding to a first one of the plurality of frequencies.
  • one of the plurality of off-diagonal terms is a ratio of a first corrected in-phase component to a second corrected in-phase component of the plurality of corrected in-phase components, and the first corrected in-phase component corresponds to The first frequency.
  • one of the plurality of off-diagonal terms is a ratio of a first corrected orthogonal component to a second corrected orthogonal component of the plurality of corrected orthogonal components, the first correction The orthogonal component corresponds to the first frequency.
  • the first frequency is multiplied by a time interval as an integer, and the time interval is a window function interval of the window function or an integral interval of the integral.
  • the embodiment of the present application provides a non-orthogonal demodulation method, which is applied to a touch system, where the touch system includes a plurality of transmitting electrodes and a plurality of receiving electrodes, wherein
  • the non-orthogonal demodulation method includes: transmitting a plurality of transmission signals to the plurality of transmission electrodes respectively at a first time, the plurality of transmission signals corresponding to a plurality of frequencies, and the plurality of transmission signals are not between each other Orthogonal; at the first time, receiving a received signal from a first one of the plurality of receiving electrodes; mixing and integrating the received signal on the plurality of frequencies to generate a corresponding And a plurality of in-phase components and a plurality of orthogonal components of the plurality of frequencies; and generating at least one decoding matrix, and calculating according to the at least one decoding matrix, the plurality of in-phase components, and the plurality of orthogonal components Corresponding to a plurality of energies
  • the embodiment of the present application uses a decoding matrix to demodulate a non-orthogonal transmission signal to calculate energy corresponding to a plurality of transmission signals, and determine coordinates at which a touch event occurs. Compared to the prior art, the present application has the advantage of a smaller signal band.
  • FIG. 1 is a schematic diagram of a touch system according to an embodiment of the present application.
  • FIG. 2 is a schematic diagram of a non-orthogonal demodulation module according to an embodiment of the present application
  • FIG. 3 is a schematic diagram of a decoding process according to Embodiment 1 of the present application.
  • FIG. 4 is a schematic diagram of a touch process according to an embodiment of the present application.
  • FIG. 5 is a schematic diagram of a calibration process according to Embodiment 1 of the present application.
  • Figure 6 is a spectrum of two mutually orthogonal signals.
  • FIG. 1 is a schematic diagram of a touch system 10 according to Embodiment 1 of the present application.
  • the touch system 10 includes transfer electrodes TE1 to TEM, reception electrodes RE1 to REN, a signal generation module 12, and a non-orthogonal demodulation module 14.
  • the signal generating module 12 is coupled to the transmitting electrodes TE1 TEM TEM, and the signal generating module 12 can transmit the plurality of transmitting signals to the plurality of or partial transmitting electrodes of the transmitting electrodes TE1 TEM TEM at the same time.
  • the non-orthogonal demodulation module 14 is coupled to the transmitting electrodes TE1 TEM TEM, and the non-orthogonal demodulation module 14 can receive the received signals on one receiving electrode at a time in time sequence, and perform non-orthogonal solutions on the received signals. Adjusted to obtain the amplitude/energy of the receiving electrode corresponding to the plurality of transmitted signals to determine the coordinates at which the touch event occurs.
  • the amplitude of the plurality of transmitted signals is equivalent to the energy of the plurality of transmitted signals (the amplitude can be obtained by acquiring the energy, and vice versa), and in the subsequent description and the claims, the energy of the plurality of transmitted signals is obtained. The representative explained.
  • the plurality of transmitted signals may not need to be orthogonal to each other, and the plurality of transmitted signals may be multiple single frequencies.
  • multiple single frequency signals correspond to multiple frequencies.
  • the transmission signal TX m may be proportional to sin2 ⁇ f m t or cos2 ⁇ f m t, at which time the transmission signal TX m corresponds to the frequency f m .
  • the plurality of transmission signals are all single-frequency signals
  • the frequencies f m and f n of the two single-frequency transmission signals TX m and TX n are equal to an integer multiple of the reciprocal of a time interval T (ie,
  • K/T, where K is a positive integer)
  • the single-frequency transmission signals TX m and TX n are orthogonal to each other.
  • the difference between the frequencies f m and f n is less than 1/T (or not equal to K/T)
  • the single-frequency transmission signals TX m and TX n are not orthogonal to each other.
  • the time interval T may be a window function interval or an integration interval, which will be described in detail later.
  • the following signal transmission module 12 transmits two single-frequency transmission signals TX a and TX b to the two transmission electrodes TE1 and TE3 at the same time (ie, the first time), and the non-orthogonal demodulation module 14 receives
  • the reception signal RX" on the reception electrode RE2 is described as an example, and is not limited thereto.
  • ⁇ a and ⁇ b are the phases of the corresponding transmitting signals TX a and TX b at the receiving electrode RE2, respectively
  • a and B are amplitudes corresponding to the transmitted signals TX a and TX b and respectively at the receiving electrode RE 2 , A 2 , B 2 That is, the energy corresponding to the transmission signals TX a , TX b and the receiving electrode RE2, respectively.
  • the non-orthogonal demodulation module 14 can extract the energy A 2 , B 2 corresponding to the transmission signals TX a , TX b according to the received signal RX.
  • FIG. 2 is a schematic diagram of the non-orthogonal demodulation module 14 according to an embodiment of the present application.
  • the non-orthogonal demodulation module 14 includes a mixing integration unit 140 and a decoding unit 142.
  • the mixing and integrating unit 140 is configured to separately mix and integrate the received signal RX on the frequencies f a and f b to generate in-phase components I a and I b corresponding to the frequencies f a and f b .
  • quadrature components Q a , Q b quadrature components
  • the decoding unit 142 can generate decoding matrices D I and D Q corresponding to the in-phase channel (I-Channel) and the orthogonal channel (Q-Channel), and according to the decoding matrices D I , D Q , the in-phase components I a , I b , and The orthogonal components Q a , Q b calculate the energies A 2 , B 2 corresponding to the transmitted signals TX a , TX b .
  • the decoding unit 142 can be implemented by using a digital circuit or a digital signal processor (DSP).
  • the circuit structure of the mixing and integrating unit 140 is known to those skilled in the art and is briefly described below.
  • the mixing and integrating unit 140 includes mixers MXI a , MXQ a , MXI b , MXQ b , a window function unit WD, and an integrator INT, and the window function unit WD is equivalent to applying a window function g on a continuous time ( t) at the received signal RX, the mixers MXI a , MXQ a , MXI b , MXQ b multiply the output of the window function unit WD by sin2 ⁇ f a t, cos2 ⁇ f a t, sin2 ⁇ f b t, cos2 ⁇ f b t, respectively, and finally by integration
  • the INT unit integrates the outputs of the mixers MXI a , MXQ a , MXI b , and MXQ b to output the in-phase components I a and I b and
  • FIG. 3 is a schematic diagram of a decoding process 30 according to an embodiment of the present application.
  • Decoding unit 142 performs decoding process 30 to calculate energies A 2 , B 2 corresponding to transmit signals TX a , TX b .
  • the decoding process 30 includes the following steps:
  • Step 300 Arranging the in-phase components I a and I b into an in-phase vector v I and arranging the orthogonal components Q a and Q b into an orthogonal vector v Q .
  • Step 302 Obtain a matrix P I and a matrix P Q .
  • Step 304 Calculate the inverse matrix of the decoding matrix D I as the matrix P I and calculate the inverse matrix of the decoding matrix D Q as the matrix P Q .
  • Step 306 The decoding matrix D I, D Q, the in-phase and quadrature vector v I v Q vector to obtain an in-phase and a quadrature Results Results r I r Q.
  • Step 308 Calculate the energy A 2 , B 2 corresponding to the transmission signals TX a , TX b according to the in-phase result r I and the orthogonal result r Q .
  • steps 302 through 308 are briefly described below.
  • the operations performed by the mixing and integrating unit 140 on the received signal RX are linear operations
  • the in-phase components I a and I b and the orthogonal components Q a and Q b output by the mixing and integrating unit 140 are The amplitudes A and B are linear.
  • r I [r I,a , r I,b ] T
  • r Q [r Q,a ,r Q,b ] T
  • r I,a ,r Q,a are linear with amplitude A, r I,b ,r Q,b and amplitude B is linear
  • the matrices P I and P Q are used to describe the linear relationship between the in-phase components (I a , I b ) and the orthogonal components (Q a , Q b ) and r I, a , r Q, a , respectively. That is, the matrix P I is used to describe the linear relationship between the in-phase vectors v I and r I , that is, the matrix P Q is used to describe the linear relationship between the orthogonal components
  • decoding unit 142 first obtains matrix P I and matrix P Q .
  • the decoding unit 142 can calculate the energy A 2 and B 2 corresponding to the transmission signals TX a and TX b based on the in-phase result r I and the quadrature result r Q .
  • the in-phase components I a , I b and the quadrature components Q a , Q b can be expressed as Equations 1.1 to 1.4 (see later).
  • the time interval T may be a window function interval corresponding to the window function g(t) or an integral interval of the integrator
  • the window function g(t) corresponds to a window spectrum G(f)
  • the spectral value G(f a+b ) and the difference spectral value G(f ab ) respectively represent the spectral values of the window spectrum G(f) at the frequency and f a+b and the frequency difference f ab
  • G(2f a ) and G(2f b ) represents the spectral value of the window spectrum G(f) at double frequency 2f a and double frequency 2f b , respectively.
  • the in-phase components I a , I b and the orthogonal components Q a , Q b can be expressed as Equations 2.1 to 2.4.
  • the in-phase vector v I and the orthogonal vector v Q can be expressed in matrix form as Equations 3.1 and 3.2.
  • the off-diagonal entries of the matrices P I and P Q are related to the difference spectrum value G(f ab ) and the spectral value G(f a+b ), that is,
  • the off-diagonal terms of the matrices P I , P Q are related to the frequency difference f ab and the frequency and f a+b .
  • step 306 the decoding unit 142 can calculate the in-phase result r I as the formula 5.1, and calculate the orthogonal result r Q as the formula 5.2.
  • the matrices P I and P Q are obtained on the premise of ignoring the double-frequency spectrum values G(2f a ) and G(2f b ).
  • the sum spectrum value G(f a+b ) can be further ignored, that is, the decoding unit 142 can obtain the matrix P I , P Q as the formula 6 in step 302, and according to the foregoing steps 304-308.
  • the operational details are calculated by the energy A 2 , B 2 of the transmitted signals TX a , TX b .
  • the decoding unit 142 only needs a single matrix P in step 302. Steps 304-308 can be performed, and the off-diagonal terms of the matrix P are related to the difference spectral value G(f ab ), that is, the off-diagonal terms of the matrix P are related to the frequency difference f ab .
  • the representative window function unit WD does not suppress the sidelobe of its output signal, but only limits the integration interval of the integrator INT.
  • the signal generating module 12 in the touch system 10 can transmit the signals TX a , TX b to the two transmitting electrodes TE1 and TE3 at the same time, and the non-orthogonal demodulating module 14 receives the receiving signal on the receiving electrode RE2.
  • FIG. 4 is a schematic diagram of a non-orthogonal demodulation process 40 according to an embodiment of the present application.
  • the non-orthogonal demodulation process 40 is performed by the touch system 10 and includes the following steps:
  • Step 400 At a first time, the signal generating module 12 transmits the signals TX a and TX b to the transmitting electrodes TE1 and TE3, and the transmitting signals TX a and TX b are divided into corresponding frequencies f a and f b , and the signal TX a is transmitted.
  • TX b is non-orthogonal to each other.
  • Step 402 At the first time, the non-orthogonal demodulation module 14 receives the received signal RX from the receiving electrode RE2 in the receiving electrodes RE1 REN.
  • Step 404 The mixing and integrating unit 140 respectively performs mixing and integration on the received signals RX on the frequencies f a and f b to generate in-phase components I a , I b and orthogonal components Q a of the corresponding rates f a and f b . , Q b .
  • Step 406 The decoding unit 142 generates the decoding matrices D I , D Q , and calculates the energy A 2 corresponding to the transmission signals TX a , TX b according to the decoding matrices D I , D Q , the in-phase vector v I and the orthogonal vector v Q . , B 2 .
  • step 406 are the decoding process 30, and the details of the operation of the non-orthogonal demodulation process 40 can be referred to the related paragraphs, and thus will not be described again.
  • the matrixes P I and P Q can be obtained by using a calibration method to better meet the actual situation, that is, before the touch system 10 can perform the non-orthogonal demodulation process 40.
  • a calibration process is performed to obtain the matrices P I and P Q
  • the non-orthogonal demodulation process 40 is performed according to the matrices P I and P Q obtained by the calibration process to obtain corresponding to the transmitted signals TX a and TX b .
  • FIG. 5 is a schematic diagram of a calibration process 50 according to an embodiment of the present application.
  • the calibration process 50 is performed by the touch system 10 and includes the following steps:
  • Step 500 At a correction time, the signal generating module 12 transmits only the transmission signal TX a corresponding to the frequency f a to the transmitting electrode TE1 , and the non-orthogonal demodulating module 14 receives a correction signal CS through the receiving electrode RE 2 .
  • Step 502 the integral mixer unit 140 according to the correction signal CS, is generated corresponding to the frequency f a, f b correcting phase component of CI a, CI b and correcting quadrature component CQ a, CQ b.
  • Step 504 The decoding unit 142 generates the matrices P I , P Q according to the corrected in-phase components CI a , CI b and the corrected orthogonal components CQ a , CQ b .
  • the mixer 140 may generate the integral unit corresponding to the frequency f a, f b in accordance with the corrected phase component correction signal CS CI a, CI b and correcting quadrature component CQ a, CQ b Equation 10.1 to Equation 10.4 is, It should be noted that since the window function g(t) has a time interval T, the window spectrum G(f) has a zero crossing point at the integer multiple of the reciprocal of the time interval T, that is, G(f)
  • step 504 the decoding unit 142 can obtain the matrices P I and P Q as the formula 11.1 and the formula 11.2.
  • the touch system 10 can perform the non-orthogonal demodulation process 40 (or the decoding process 30) according to the matrix P I , P Q (formula 11.1, 11.2) obtained by the calibration process 50 to obtain the corresponding signal.
  • the energy A 2 , B 2 of TX a and TX b The energy A 2 , B 2 of TX a and TX b .
  • the two single-frequency transmission signals TX a and TX b are transmitted to the two transmission electrodes at a time, and the signal generation module 12 can transmit the plurality of transmission signals at most (at the same time) at most.
  • the off-diagonal terms of the matrices P I and P Q are related to the difference spectrum values G(f ab ), G(f ac ), G(f ad ), G(f bc ), G(f bd ).
  • G(f cd ) that is, the off-diagonal terms of the matrix P are related to the frequency differences f ab , f ac , f ad , f bc , f bd , f cd , and are also within the scope of the present invention.
  • the present application utilizes a decoding matrix to demodulate a non-orthogonal transmission signal to calculate energy corresponding to a plurality of transmission signals and determine coordinates at which a touch event occurs.
  • the present application has the advantage of a smaller signal band.

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Abstract

本申请提供了一种非正交解调模块，接收一接收信号，所述接收信号相关于多个传送信号的总和，所述多个传送信号对应多个频率，所述多个传送信号彼此之间非正交，所述非正交解调模块包括混频积分单元，用来对所述接收信号于所述多个频率上分别进行混频以及积分，以产生对应于所述多个频率的多个同相分量以及多个正交分量；以及解码单元，用来产生至少一解码矩阵，并根据所述至少一解码矩阵、所述多个同相分量及所述多个正交分量，计算对应于所述多个传送信号的多个能量。

Description

非正交解调模块、触控系统及非正交解调方法 技术领域
本申请涉及一种非正交解调模块、触控系统及非正交解调方法，尤其涉及一种缩小信号带宽的非正交解调模块、触控系统及非正交解调方法。
背景技术
随着科技日益进步，近年来各种电子产品的操作接口逐渐人性化。举例而言，透过触控面板，使用者可直接以手指或触控笔在屏幕上操作、输入信息/文字/图样，省去使用键盘或按键等输入设备的麻烦。实际上，触控屏通常由一感应面板及设置于感应面板后方的显示器组成。电子装置根据用户在感应面板上所触碰的位置，以及当时显示器所呈现的画面，来判断该次触碰的意涵，并执行相对应的操作结果。
现有触控技术已发展出同时(于同一时间)利用二个不同频率且相互正交的信号对触控系统的二个传送电极进行打码(即传送二个信号至二个电极)，由于打码信号彼此之间相互正交，在解调过程中可分辨出于不同频率所承载的信号。图6所示的二个相互正交的信号频谱，其频率分别为fa及fb，对应二相互正交信号的信号频率需相互保持一特定频率间隔，才能维持其相互正交的特性。然而，若传送二个或多个相互正交的信号，其信号所占用的带宽(简称信 号带宽)较大，且需确保信号带宽内无其他干扰，而增加触控系统设计的难度。
因此，如何在同时传送多个信号至多个电极的情况下缩小信号带宽，就成为业界所努力的目标之一。
发明内容
因此，本申请部分实施例的目的即在于提供一种缩小信号带宽的非正交解调模块、触控系统及非正交解调方法，以改善现有技术的缺点。
为了解决上述技术问题，本申请实施例提供了一种非正交解调模块，对一接收信号进行解调。所述接收信号相关于多个传送信号的总和，所述多个传送信号对应多个频率，所述多个传送信号彼此之间非正交，所述非正交解调模块包括混频积分单元，用来对所述接收信号于所述多个频率上分别进行混频以及积分，以产生对应于所述多个频率的多个同相分量以及多个正交分量；以及解码单元，用来产生至少一解码矩阵，并根据所述至少一解码矩阵、所述多个同相分量及所述多个正交分量，计算对应于所述多个传送信号的多个能量。
例如，所述解码单元用来执行以下步骤：将所述多个同相分量(In-phase Component)排列成一同相向量，并将所述多个正交分量(Quadrature Component)排列成一正交向量；取得至少一矩阵，其中所述至少一矩阵具有多个非对角项，所述多个非对角项相关于至少一频率差，所述至少一频率差为所述多个频率中二个频率的差；计算所述至少一解码矩阵，所述至少一解码矩 阵正比于所述至少一矩阵的反矩阵；根据所述至少一解码矩阵、所述同相向量及所述正交向量，取得一同相结果及一正交结果；以及根据所述同相结果及所述正交结果，计算应于所述多个传送信号的所述多个能量。
例如，所述多个非对角项相关于所述至少一频率差以及至少一频率和，所述至少一频率和为所述多个频率中二个频率的和。
例如，所述混频积分单元施加一窗函数于所述接收信号，所述窗函数对应一窗频谱，所述多个非对角项相关于至少一差频谱值，所述至少一差频谱值为所述窗频谱对应于所述至少一频率差的频谱值。
例如，所述多个非对角项相关于所述至少一差频谱值以及至少一和频谱值，所述至少一和频谱值为所述窗频谱对应于至少一频率和的频谱值，所述至少一频率和为所述多个频率中二个频率的和。
为了解决上述技术问题，本申请实施例提供了一种触控系统，包括多个传送电极；多个接收电极；信号产生模块，耦接于所述多个传送电极，于一第一时间，所述信号产生模块分别将多个传送信号传送到所述多个传送电极，所述多个传送信号对应多个频率，所述多个传送信号彼此之间非正交；以及非正交解调模块，耦接于所述多个传送电极，于所述第一时间，所述非正交解调模块接收所述多个接收电极中一第一接收电极的一接收信号，所述非正交解调模块包括混频积分单元，用来对所述接收信号于所述多个频率上分别进行混频以及 积分，以产生对应于所述多个频率的多个同相分量以及多个正交分量；以及解码单元，用来产生至少一解码矩阵，并根据所述至少一解码矩阵、所述多个同相分量及所述多个正交分量，计算对应于所述多个传送信号的多个能量。
例如，于一校正时间，所述信号产生模块将一第一传送信号传送到所述多个传送电极中的一第一传送电极，所述非正交解调模块由所述第一接收电极接收一校正信号，所述混频积分单元根据所述校正信号产生对应于所述多个频率的多个校正同相分量以及多个校正正交分量，所述解码单元根据所述多个校正同相分量或所述校正正交分量，产生所述至少一矩阵，所述第一传送信号对应所述多个频率中一第一频率。
例如，所述多个非对角项中的一非对角项为所述多个校正同相分量中一第一校正同相分量与一第二校正同相分量的比值，所述第一校正同相分量对应所述第一频率。
例如，所述多个非对角项中的一非对角项为所述多个校正正交分量中一第一校正正交分量与一第二校正正交分量的比值，所述第一校正正交分量对应所述第一频率。
例如，所述第一频率乘以一时间区间为一整数，所述时间区间为所述窗函数的一窗函数区间或所述积分的一积分区间。
为了解决上述技术问题，本申请实施例提供了一种非正交解调方法，应用于一触控系统，所述触控系统包括多个传送电极及多个接收电极，其特征在于，所述非正交解调方法包括：于一第一时间，将多个传送信号分别传送到所述多个传送电极，所述多个传送信号对应多个频率，所述多个传送信号彼此之间非正交；于所述第一时间，由所述多个接收电极中一第一接收电极接收一接收信号；对所述接收信号于所述多个频率上分别进行混频以及积分，以产生对应于所述多个频率的多个同相分量以及多个正交分量；以及产生至少一解码矩阵，并根据所述至少一解码矩阵、所述多个同相分量及所述多个正交分量，计算对应于所述多个传送信号的多个能量。
本申请实施例利用解码矩阵来对非正交的传送信号进行解调，以计算出对应于多个传送信号的能量，判断触碰事件发生的坐标。相较于现有技术，本申请具有较小信号频带的优点。
附图说明
图1为本申请实施例一触控系统的示意图；
图2为本申请实施例一非正交解调模块的示意图；
图3为本申请实施例一解码流程的示意图；
图4为本申请实施例一触控流程的示意图；
图5为本申请实施例一校正流程的示意图；
图6为二相互正交信号的频谱。
具体实施方式
为了使本申请的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本申请进行进一步详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本申请，并不用于限定本申请。
请参考图1，图1为本申请实施例一的触控系统10的示意图。触控系统10包含传送电极TE1～TEM、接收电极RE1～REN、信号产生模块12以及非正交(Non-orthogonal)解调模块14。信号产生模块12耦接于传送电极TE1～TEM，信号产生模块12可在同一时间将多个传送信号分别传送至传送电极TE1～TEM其中的多个或者部分传送电极。非正交解调模块14耦接于传送电极TE1～TEM，非正交解调模块14可按照时间顺序，一次接收一个接收电极上的接收信号，并对所接收的接收信号进行非正交解调，取得于接收电极对应于该多个传送信号的振幅/能量，以判断触碰事件发生的坐标。由于取得该多个传送信号的振幅相当于取得该多个传送信号的能量(取得能量即可取得振幅，反之亦然)，在后续说明书以及权利要求中，以取得该多个传送信号的能量为代表说明之。
另外，为了缩小该多个传送信号所需的频谱(即缩小信号频带)，该多个传送信号彼此之间可不需相互正交(Mutually Orthogonal)，该多个传送信号可皆为多个单频信号，多个单频信号对应多个频率。举例来说，在忽略相位的情况下，传送信号TXm可正比于sin2πfmt或是cos2πfmt，此时传送信号TXm对应频率fm。在多个传送信号为皆为单频信号的情况下，当二个单频传送信号TXm、TXn的频率fm、fn之间的差等于一时间区间T倒数的整数倍(即|fm－fn|＝K/T， 其中K为正整数)时，单频传送信号TXm、TXn即为相互正交。反之，若频率fm、fn之间的差小于1/T(或不等于K/T)，单频传送信号TXm、TXn彼此之间不相互正交。其中，时间区间T可为窗函数区间或积分区间，将详述于后。
为了方便说明，以下以「于同一时间(即第一时间)信号产生模块12传送二个单频传送信号TXa、TXb至二个传送电极TE1、TE3，且非正交解调模块14接收接收电极RE2上的接收信号RX」为例进行说明，而不限于此。假设二个单频传送信号为TXa＝sin2πfat和TXb＝sin2πfbt，则接收信号RX可表示为RX＝Asin(2πfat+θa)+Bsin(2πfbt+θb)，其中θa、θb分别为对应传送信号TXa、TXb在接收电极RE2的相位，A、B分别为对应传送信号TXa、TXb且于接收电极RE2的振幅，A2、B2即分别为对应传送信号TXa、TXb且于接收电极RE2的能量。非正交解调模块14可根据接收信号RX，解出对应传送信号TXa、TXb的能量A2、B2。
详细来说，请参考图2，图2为本申请实施例非正交解调模块14的示意图。非正交解调模块14包括混频积分单元140以及解码(Decoding)单元142。混频积分单元140用来对接收信号RX于频率fa、fb上分别进行混频以及积分，以产生对应于频率fa、fb的同相分量(In-phase Component)Ia、Ib以及正交分量(Quadrature Component)Qa、Qb。解码单元142可产生对应于同相通道(I-Channel)及正交通道(Q-Channel)的解码矩阵DI以及DQ，并根据解码矩阵DI、DQ、同相分量Ia、Ib及正交分量Qa、Qb，计算对应于传送信号TXa、TXb的能量A2、B2。其中，解码单元142可利用数字电路或是数字信号处理器(Digital  Signal Processor，DSP)实现。
混频积分单元140的电路结构为本领域具通常知识者所知，故简述如下。混频积分单元140包括混频器MXIa、MXQa、MXIb、MXQb、窗函数单元WD以及积分器INT，窗函数单元WD相当于在连续时间(continuous time)上施加一窗函数g(t)于接收信号RX，混频器MXIa、MXQa、MXIb、MXQb分别将窗函数单元WD的输出乘以sin2πfat、cos2πfat、sin2πfbt、cos2πfbt，最后由积分器INT分别对混频器MXIa、MXQa、MXIb、MXQb的输出进行积分，即可输出同相分量Ia、Ib及正交分量Qa、Qb。
请参考图3，图3为本申请实施例一解码流程30的示意图。解码单元142执行解码流程30，以计算对应于传送信号TXa、TXb的能量A2、B2。解码流程30包括以下步骤：
步骤300：将同相分量Ia、Ib排列成一同相向量vI，并将正交分量Qa、Qb排列成一正交向量vQ。
步骤302：取得一矩阵PI以及一矩阵PQ。
步骤304：计算解码矩阵DI为矩阵PI的反矩阵，并计算解码矩阵DQ为矩阵PQ的反矩阵。
步骤306：根据解码矩阵DI、DQ、同相向量vI以及正交向量vQ以取得一同相结果rI及一正交结果rQ。
步骤308：根据同相结果rI及正交结果rQ，计算对应于传送信号TXa、TXb的能量A2、B2。
于步骤300中，解码单元142可形成同相向量vI为vI＝[Ia,Ib]T，并形成正交向量vQ为vQ＝[Qa,Qb]T。
步骤302至步骤308的原理简述如下。一般来说，由于混频积分单元140对接收信号RX所进行的运算皆是线性运算，因此，混频积分单元140所输出的同相分量Ia、Ib及正交分量Qa、Qb与振幅A、B之间呈线性关系。以向量/矩阵的形式来说，同相向量vI可表示为vI＝PIrI，正交向量vQ可表示为vQ＝PQrQ，其中rI＝[rI,a,rI,b]T且rQ＝[rQ,a,rQ,b]T，rI,a、rQ,a与振幅A呈线性关系，rI,b、rQ,b与振幅B呈线性关系，矩阵PI和PQ分别用来描述同相分量(Ia、Ib)及正交分量(Qa、Qb)与rI,a、rQ,a之间的线性关系，亦即矩阵PI用来描述同相向量vI与rI之间的线性关系，即矩阵PQ用来描述正交向量vQ与rQ之间的线性关系。
简单来说，于步骤302中，解码单元142先取得矩阵PI以及矩阵PQ。于步骤304中，解码单元142计算解码矩阵DI使其正比于矩阵PI的反矩阵(即DI＝c(PI)-1)，并计算解码矩阵DQ使其正比于矩阵PQ的反矩阵(即DQ＝c(PQ)-1),其中c为一常数，为求简洁，以下假设常数c＝1，但实际应用中该常数c不受此限制。。于步骤306中，解码单元142可将解码矩阵DI乘以同相向量vI而得到同相结果rI(DIvI＝rI)，并将解码矩阵DQ乘以正交向量vQ而得到正交结果rQ(DQvQ＝rQ)。如以一来，于步骤308中，解码单元142即可根据同相结果rI及正交结果rQ，计算对应于传送信号TXa、TXb的能量A2、B2。
详细来说，同相分量Ia、Ib及正交分量Qa、Qb可表示为公式1.1～公式1.4(请参看后文)。其中，假设窗函数g(t)在t小于(－T/2)或大于T/2时为0，即
Figure PCTCN2017107757-appb-000001
时间区间T可为对应窗函数g(t)的窗函数区间或是积分器的积分区间，窗函数g(t)对应一窗频谱G(f)，窗频谱G(f)为窗函数g(t)的傅立叶变换(Fourier Transform)，即G(f)＝∫g(t)e-j2πftdt。另外，频率和fa+b代表频率fa、fb的和，其可表示为fa+b＝fa+fb，频率差fa-b代表频率fa、fb的差，其可表示为fa-b＝fa-fb。和频谱值G(fa+b)及差频谱值G(fa-b)分别代表窗频谱G(f)于频率和fa+b及频率差fa-b的频谱值，而G(2fa)及G(2fb)分别代表窗频谱G(f)于双倍频2fa及双倍频2fb的频谱值。
Figure PCTCN2017107757-appb-000002
Figure PCTCN2017107757-appb-000003
Figure PCTCN2017107757-appb-000004
Figure PCTCN2017107757-appb-000005
在忽略双倍频频谱值G(2fa)、G(2fb)的情况下，同相分量Ia、Ib及正交分量Qa、Qb可表示为公式2.1～公式2.4。
Figure PCTCN2017107757-appb-000006
Figure PCTCN2017107757-appb-000007
Figure PCTCN2017107757-appb-000008
Figure PCTCN2017107757-appb-000009
换句话说，同相向量vI及正交向量vQ以矩阵形式可表示为公式3.1、3.2。
Figure PCTCN2017107757-appb-000010
Figure PCTCN2017107757-appb-000011
在一实施例中，于步骤302中，解码单元142可取得矩阵PI如公式4.1，并可取得矩阵PQ如公式4.2，并于步骤304中，解码单元142可计算DI＝(PI)-1以及DQ＝(PQ)-1。由公式4.1、4.2可知，矩阵PI、PQ的非对角项(off-diagonal entries)皆相关于差频谱值G(fa-b)以及和频谱值G(fa+b)，也就是说，矩阵PI、PQ的非对角项相关于频率差fa-b以及频率和fa+b。
Figure PCTCN2017107757-appb-000012
Figure PCTCN2017107757-appb-000013
如此一来，于步骤306中，解码单元142可计算同相结果rI为公式5.1，并计算正交结果rQ为公式5.2。
Figure PCTCN2017107757-appb-000014
Figure PCTCN2017107757-appb-000015
根据公式3.1、3.2，同相结果rI中的rI,a及rI,b代表rI,a＝(AT/2)cosθa及rI,b＝(BT/2)cosθb，正交结果rQ中的rQ,a及rQ,b代表rQ,a＝(AT/2)sinθa及rQ,b＝(BT/2)sinθb。如此一来，于步骤308中，解码单元142可取得(AT/2)2＝(rI,a)2+(rQ,a)2以及(BT/2)2＝(rI,b)2+(rQ,b)2，另外，时间区间T对解码单元142来说为已知，因此，解码单元142可根据同相结果rI及正交结果rQ，计算应于传送信号TXa、TXb的能量A2、B2。
前述实施例是在忽略双倍频频谱值G(2fa)、G(2fb)的前提下，取得矩阵PI、PQ。于另一实施例中，可进一步忽略和频谱值G(fa+b)，也就是说，解码单元142于步骤302可取得矩阵PI、PQ为公式6，并依照前述步骤304～308的操作细节， 计算应于传送信号TXa、TXb的能量A2、B2。
Figure PCTCN2017107757-appb-000016
需注意的是，在忽略双倍频频谱值G(2fa)、G(2fb)以及和频谱值G(fa+b)的前提下，解码单元142于步骤302仅需单一矩阵P即可执行述步骤304～308，而矩阵P的非对角项相关于差频谱值G(fa-b)，也就是说，矩阵P的非对角项相关于频率差fa-b。
举例来说，窗函数g(t)可为一矩形窗(rectangular window)，即窗函数g(t)可表示为g(t)＝rect(t/T)，即
Figure PCTCN2017107757-appb-000017
代表窗函数单元WD并未对其输出信号的旁波带(sidelobe)进行抑制，而仅限制积分器INT的积分区间。在此情形下，矩阵PI、PQ可表示为公式7.1、7.2(忽略双倍频频谱值)、公式8(忽略双倍频频谱值及和频谱值)或公式9.1、9.2(保留双倍频频谱值及和频谱值)，其中sinc(x)＝sin(πx)/(πx)。
Figure PCTCN2017107757-appb-000018
Figure PCTCN2017107757-appb-000019
Figure PCTCN2017107757-appb-000020
Figure PCTCN2017107757-appb-000021
Figure PCTCN2017107757-appb-000022
简言之，触控系统10中的信号产生模块12可于同一时间将传送信号TXa、TXb至二个传送电极TE1、TE3，非正交解调模块14接收接收电极RE2上的接收信号RX，混频积分单元140产生对应率fa、fb的同相分量Ia、Ib及正交分量Qa、Qb，解码单元142透过执行解码流程30，取得矩阵PI、PQ，并计算解码矩阵DI、DQ分别为矩阵PI、PQ的反矩阵，并根据解码矩阵DI、DQ，计算对应于传送信号TXa、TXb的能量A2、B2。关于触控系统10的操作，可归纳成一非正交解调流程。请参考图4，图4为本申请实施例一非正交解调流程40的示意图。非正交解调流程40由触控系统10来执行，其包括以下步骤：
步骤400：于一第一时间，信号产生模块12将传送信号TXa、TXb至传送电极TE1、TE3，传送信号TXa、TXb分于对应频率fa、fb，传送信号TXa、TXb彼此之间非正交。
步骤402：于所述第一时间，非正交解调模块14由接收电极RE1～REN中的接收电极RE2接收接收信号RX。
步骤404：混频积分单元140对接收信号RX于频率fa、fb上分别进行混频以及积分，以产生对应率fa、fb的同相分量Ia、Ib及正交分量Qa、Qb。
步骤406：解码单元142产生解码矩阵DI、DQ，并根据解码矩阵DI、DQ、同相向量vI以及正交向量vQ，计算对应于传送信号TXa、TXb的能量A2、B2。
其中，步骤406的操作细节即为解码流程30，而其余关于非正交解调流程40的操作细节可参考前述相关段落，故于此不再赘述。
另一方面，在实际应用中，信号产生模块12与非正交解调模块14之间可能具有其他通道效应。因此，于一实施例中，矩阵PI、PQ可利用校正(Calibration)的方式取得，以更符合实际情况，也就是说，触控系统10可于执行非正交解调流程40之前，先执行一校正流程，以取得矩阵PI、PQ，之后再根据校正流程所得的矩阵PI、PQ，执行非正交解调流程40，以取得对应于传送信号TXa、TXb的能量A2、B2。
详细来说，请参考图5，图5为本申请实施例一校正流程50的示意图。校正流程50由触控系统10来执行，其包括以下步骤：
步骤500：于一校正时间，信号产生模块12仅将对应于频率fa的传送信号TXa传送到传送电极TE1，非正交解调模块14通过接收电极RE2接收一校正信号CS。
步骤502：混频积分单元140根据校正信号CS，产生对应于频率fa、fb的校正同相分量CIa、CIb以及校正正交分量CQa、CQb。
步骤504：解码单元142根据校正同相分量CIa、CIb以及校正正交分量CQa、CQb，产生矩阵PI、PQ。
于步骤500中，信号产生模块12于校正时间中(校正时间位于第一时间之前)仅将对应于频率fa的传送信号TXa传送到传送电极TE1(如传送信号TXa 可表示为TXa＝sin2πfat)，非正交解调模块14于校正时间由接收电极RE2接收到的校正信号CS可表示为CS＝Asin(2πfat+θa)，另外，可选定频率fa为时间区间T倒数的整数倍(即fa＝K/T)，即频率fa乘以时间区间T为一整数。
于步骤502中，混频积分单元140根据校正信号CS可产生对应于频率fa、fb的校正同相分量CIa、CIb以及校正正交分量CQa、CQb为公式10.1～公式10.4，需注意的是，因窗函数g(t)具有时间区间T，窗频谱G(f)在频率f为时间区间T倒数的整数倍处有过零点(zero crossing point)，即G(f)|f＝K/T＝0，换句话说，在频率fa为时间区间T倒数的整数倍的情况下，双倍频频谱值G(2fa)等于0。
Figure PCTCN2017107757-appb-000023
Figure PCTCN2017107757-appb-000024
Figure PCTCN2017107757-appb-000025
Figure PCTCN2017107757-appb-000026
如此一来，于步骤504中，解码单元142可取得矩阵PI、PQ为公式11.1、公式11.2。
Figure PCTCN2017107757-appb-000027
Figure PCTCN2017107757-appb-000028
换句话说，透过校正流程50，触控系统10可仅将传送信号TXa＝sin2πfat传送到传送电极TE1，而取得于校正时间的校正同相分量CIa、CIb以及校正正交分量CQa、CQb，并据以取得PI、PQ如公式11.1、11.2。如此一来，触控系统10可根据校正流程50所取得的矩阵PI、PQ(公式11.1、11.2)，执行非正交解调流程40(或解码流程30)，以取得对应于传送信号TXa、TXb的能量A2、B2。
需注意的是，前述实施例用以说明本发明之概念，本领域具通常知识者当可据以做不同的修饰，而不限于此。举例来说，以上实施例皆以一次传送二个单频传送信号TXa、TXb至二个传送电极，而不限于此，信号产生模块12可一次(于同一时间)传送多个传送信号至多个传送电极，例如，信号产生模块12可一次(于同一时间)传送TXa、TXb、TXc、TXd至四个传送电极，接收信号RX可表示为RX＝Asin(2πfat+θa)+Bsin(2πfbt+θb)+Csin(2πfct+θc)+Dsin(2πfdt+θd)，其中θa、θb、θa、θb分别为对应传送信号TXa、TXb、TXc、TXd且于接收电极的相位，A、B、C、D分别为对应传送信号TXa、TXb、TXc、TXd且于接收电极的振幅，A2、B2、C2、D2即分别为对应传送信号TXa、TXb、TXc、TXd且于接收电极的能量，对应于频率fa、fb、fc、fd的同相分量Ia、Ib、Ic、Id以及正交分量Qa、Qb、Qc、Qd可表示为公式12.1～12.8(忽略双倍频频谱值及和频谱值，其中频率差fx-y代表频率fx、fy的差，其可表示为fx-y＝fx-fy)，同相向量vI及正交向量vQ以矩阵形式可表示为公式13.1、13.2，矩阵PI、PQ可表示为公式14。需注意的是，矩阵PI、PQ的非对角项相关于差频谱值G(fa-b)、G(fa-c)、G(fa-d)、G(fb-c)、G(fb-d)、G(fc-d)，也就是说，矩阵P的非对角项相关于频率差fa-b、 fa-c、fa-d、fb-c、fb-d、fc-d，亦属于本发明的范畴。
Figure PCTCN2017107757-appb-000029
Figure PCTCN2017107757-appb-000030
Figure PCTCN2017107757-appb-000031
Figure PCTCN2017107757-appb-000032
Figure PCTCN2017107757-appb-000033
Figure PCTCN2017107757-appb-000034
Figure PCTCN2017107757-appb-000035
Figure PCTCN2017107757-appb-000036
Figure PCTCN2017107757-appb-000037
Figure PCTCN2017107757-appb-000038
Figure PCTCN2017107757-appb-000039
综上所述，本申请利用解码矩阵来对非正交的传送信号进行解调，以计算出对应于多个传送信号的能量，判断触碰事件发生的坐标。相较于现有技术，本申请具有较小信号频带的优点。
以上所述仅为本申请的部分实施例而已，并不用以限制本申请，凡在本申请的精神和原则之内所作的任何修改、等同替换和改进等，均应包含在本申请的保护范围之内。

Claims (18)

  1. 一种非正交解调模块，用于对一接收信号进行解调，所述接收信号相关于多个传送信号的总和，所述多个传送信号分别对应多个频率，所述多个传送信号彼此之间非正交，其特征在于，所述非正交解调模块包括：
    混频积分单元，用于对所述接收信号于所述多个频率上分别进行混频以及积分，以产生对应于所述多个频率的多个同相分量以及多个正交分量；以及
    解码单元，用于产生至少一解码矩阵，并根据所述至少一解码矩阵、所述多个同相分量及所述多个正交分量，计算对应于所述多个传送信号的多个能量。
  2. 如权利要求1所述的非正交解调模块，其特征在于，所述解码单元用于执行以下步骤：
    将所述多个同相分量排列成一同相向量，并将所述多个正交分量排列成一正交向量；
    取得至少一矩阵，其中所述至少一矩阵具有多个非对角项，所述多个非对角项相关于至少一频率差，所述至少一频率差为所述多个频率中二个频率的差；
    计算所述至少一解码矩阵，所述至少一解码矩阵相关于所述至少一矩阵的反矩阵；根据所述至少一解码矩阵、所述同相向量及所述正交向量，取得一同相结果及一正交结果；以及
    根据所述同相结果及所述正交结果，计算应于所述多个传送信号的所述多个能量。
  3. 如权利要求2所述的非正交解调模块，其特征在于，所述多个非对角项相关于所述至少一频率差以及至少一频率和，所述至少一频率和为所述多个频率中二个频率的和。
  4. 如权利要求2所述的非正交解调模块，其特征在于，所述混频积分单元施加一窗函数于所述接收信号，所述窗函数对应一窗频谱，所述多个非对角项相关于至少一差频谱值，所述至少一差频谱值为所述窗频谱对应于所述至少一频率差的频谱值。
  5. 如权利要求4所述的非正交解调模块，其特征在于，所述多个非对角项相关于所述至少一差频谱值以及至少一和频谱值，所述至少一和频谱值为所述窗频谱对应于至少一频率和的频谱值，所述至少一频率和为所述多个频率中二个频率的和。
  6. 一种触控系统，其特征在于，包括：
    多个传送电极；
    多个接收电极；
    信号产生模块，耦接于所述多个传送电极，于一第一时间，所述信号产生模块分别将多个传送信号传送到所述多个传送电极，所述多个传送信号对应多个频率，所述多个传送信号彼此之间非正交；以及
    非正交解调模块，耦接于所述多个传送电极，于所述第一时间，所述非正交解调模块接收所述多个接收电极中一第一接收电极的一接收信号；
    其中，所述正交解调模块为权利要求1-5中任意一项所述的非正交解调模块。
  7. 如权利要求6所述的触控系统，其特征在于，于一校正时间，所述信号产生模块将一第一传送信号传送到所述多个传送电极中的一第一传送电极，所述非正交解调模块通过所述第一接收电极接收一校正信号，所述混频积分单元根据所述校正信号产生对应于所述多个频率的多个校正同相分量以及多个校正正交分量，所述解码单元根据所述多个校正同相分量或所述校正正交分量，产生所述至少一矩阵，所述第一传送信号对应所述多个频率中一第一频率。
  8. 如权利要求7所述的触控系统，其特征在于，所述多个非对角项中的一非对角项为所述多个校正同相分量中一第一校正同相分量与一第二校正同相分量的比值，所述第一校正同相分量对应所述第一频率。
  9. 如权利要求7所述的触控系统，其特征在于，所述多个非对角项中的一非对角项为所述多个校正正交分量中一第一校正正交分量与一第二校正正交分量的比值，所述第一校正正交分量对应所述第一频率。
  10. 如权利要求7所述的触控系统，其特征在于，所述第一频率乘以一时间区间为一整数，所述时间区间为所述窗函数的一窗函数区间或所述积分的一积分区间。
  11. 一种非正交解调方法，应用于一触控系统，所述触控系统包括多个传送电极及多个接收电极，其特征在于，所述非正交解调方法包括：
    于一第一时间，将多个传送信号分别传送到所述多个传送电极，所述多个传送信号对应多个频率，所述多个传送信号彼此之间非正交；
    于所述第一时间，由所述多个接收电极中一第一接收电极接收一接收信号；
    对所述接收信号于所述多个频率上分别进行混频以及积分，以产生对应于所述多个频率的多个同相分量以及多个正交分量；以及
    产生至少一解码矩阵，并根据所述至少一解码矩阵、所述多个同相分量及所述多个正交分量，计算对应于所述多个传送信号的多个能量。
  12. 如权利要求11所述的非正交解调方法，其特征在于，产生所述至少一解码矩阵，并根据所述至少一解码矩阵、所述多个同相分量及所述多个正交分量，计算对应于所述多个传送信号的多个能量的步骤包括：
    将所述多个同相分量排列成一同相向量，并将所述多个正交分量排列成一正交向量；
    取得至少一矩阵，其中所述至少一矩阵具有多个非对角项，所述多个非对角项相关于至少一频率差，所述至少一频率差为所述多个频率中二个频率的差；
    计算所述至少一解码矩阵，所述至少一解码矩阵正比于所述至少一矩阵的反矩阵；
    根据所述至少一解码矩阵、所述同相向量及所述正交向量，取得一同相结果及一正交结果；以及
    根据所述同相结果及所述正交结果，计算应于所述多个传送信号的所述多个能量。
  13. 如权利要求12所述的非正交解调方法，其特征在于，所述多个非对角项相关于所述至少一频率差以及至少一频率和，所述至少一频率和为所述多个频率中二个频率的和。
  14. 如权利要求12所述的非正交解调方法，其特征在于，所述多个非对角项相关于至少一差频谱值，所述至少一差频谱值为一窗频谱对应于所述至少一频率差的频谱值。
  15. 如权利要求14所述的非正交解调方法，其特征在于，所述多个非对角项相关于所述至少一差频谱值以及至少一和频谱值，所述至少一和频谱值为所 述窗频谱对应于至少一频率和的频谱值，所述至少一频率和为所述多个频率中二个频率的和。
  16. 如权利要求12所述的非正交解调方法，其特征在于，进一步包括：
    于一校正时间，将一第一传送信号传送到所述多个传送电极中的一第一传送电极，其中所述第一传送信号对应所述多个频率中一第一频率；
    由所述第一接收电极接收一校正信号；
    根据所述校正信号，产生对应于所述多个频率的多个校正同相分量以及多个校正正交分量；以及
    根据所述多个校正同相分量或所述校正正交分量，产生所述至少一矩阵。
  17. 如权利要求16所述的非正交解调方法，其特征在于，进一步包括：
    取得所述多个非对角项中的一非对角项为所述多个校正同相分量中一第一校正同相分量与一第二校正同相分量的比值，其中所述第一校正同相分量对应所述第一频率。
  18. 如权利要求16所述的非正交解调方法，其特征在于，进一步包括：
    取得所述多个非对角项中的一非对角项为所述多个校正正交分量中一第一校正正交分量与一第二校正正交分量的比值，其中所述第一校正正交分量对应所述第一频率。
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CN107980114B (zh) 2021-10-26
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