WO2019039268A1

WO2019039268A1 - Dynamoelectric machine control device

Info

Publication number: WO2019039268A1
Application number: PCT/JP2018/029653
Authority: WO
Inventors: 藤井　淳
Original assignee: 株式会社デンソー
Priority date: 2017-08-21
Filing date: 2018-08-07
Publication date: 2019-02-28
Also published as: JP2019037101A

Abstract

A control device (30) to be used in a system equipped with a dynamoelectric machine (10) having multi-phase winding groups (14, 15), and power inverter circuits (INV1, INV2) for applying a voltage to the winding groups by alternatingly turning on upper and lower arm switches (SUp1-SWp2, SUn1-SWn2). The control device is equipped with: an adjustment unit (32) for adjusting the pulse width, which is the on-operation interval of each of the upper and lower arm switches in one electrical angle cycle of the dynamoelectric machine; and operation units (33, 34) for turning the upper and lower arm switches on one at a time during one electrical angle cycle in a manner such that the on-operation interval of each of the upper and lower arm switches during one electrical angle cycle equals the adjusted pulse width set by the adjustment unit, while satisfying a first condition that there is no overlap in the on-operation intervals of the upper arm switches corresponding to each phase, and a second condition that there is no overlap in the on-operation intervals of the lower arm switches corresponding to each phase.

Description

Control device of rotating electric machine

Cross-reference to related applications

This application is based on Japanese Patent Application No. 2017-158828 filed on Aug. 21, 2017, the contents of which are incorporated herein by reference.

The present disclosure relates to a control device of a rotating electrical machine.

As a control device of this type, as disclosed in Patent Document 1, there is known one in which the upper and lower arm switches of the power conversion circuit are alternately turned on by 180-degree conduction control. The controller applies the voltage applied to the winding of the rotating electrical machine connected to the power conversion circuit to the upper and lower arm switches in a cycle sufficiently shorter than the electrical angle half cycle of the rotating electrical machine during the ON operation period of the upper arm switch. Adjust by alternately turning on.

JP, 2017-17867, A

However, if the upper and lower arm switches are alternately turned on with a cycle sufficiently shorter than the electrical angle half cycle, electromagnetic noise and switching loss may increase.

An object of the present disclosure is to provide a control device of a rotating electrical machine capable of reducing electromagnetic noise and switching loss.

The first disclosure has a series connection of a rotating electric machine having multi-phase winding groups and an upper arm switch and a lower arm switch, and the upper arm switch and the lower arm switch are alternately turned on. And a power conversion circuit that applies a voltage to the winding group. According to a first disclosure, an adjustment unit that adjusts a pulse width which is an on operation period of each of the upper arm switch and the lower arm switch in one electrical angle cycle of the rotating electric machine, and the upper arm switch corresponding to each phase Under the first condition that the on operation period is not overlapped, and the second condition that the on operation period of the lower arm switch corresponding to each phase is not overlapped, the upper arm switch and the above in one electrical angle cycle are An operation unit for turning on the upper arm switch and the lower arm switch once each in one electrical angle cycle so that the on-operation period of each lower arm switch is the pulse width adjusted by the adjustment unit; Prepare.

According to the first disclosure, the applied voltage of the winding can be adjusted by adjusting the pulse width. Therefore, electromagnetic noise and switching loss can be reduced.

In a second disclosure, the rotating electrical machine includes a plurality of winding groups, and the power conversion circuit applies a voltage to each of the plurality of winding groups, and each of the plurality of winding groups forms one another. The electrical angle is shifted, and the operation unit imposes the first condition and the second condition in each of the plurality of winding groups, and the upper arm switch and the lower arm switch in one electrical angle cycle The upper arm switch and the lower arm switch are each turned on once in one electrical angle cycle so that each on operation period has the pulse width adjusted by the adjustment unit.

Before describing the control device of the second disclosure, a control device of a comparative example will be described. The control device of the comparative example is applied to a system including a rotating electrical machine having one multi-phase winding group. The control device of the comparative example has a configuration in which the upper arm switch and the lower arm switch are turned on once each in one electrical angle cycle, under the first condition and the second condition. In this configuration, if it is attempted to adjust the voltage applied to the winding by adjusting the pulse width which is the on operation period of each of the upper arm switch and the lower arm switch in one electrical angle cycle, the torque ripple of the rotating electrical machine increases. . Specifically, since the first and second conditions are imposed, when the on-operation period is shortened, the non-energization period to the winding appears. As a result, torque ripple of the rotating electrical machine is increased.

Therefore, the second disclosure is applied to a system including a rotating electrical machine having a plurality of multi-phase winding groups. And the electrical angle which each of a plurality of winding groups makes mutually is shifted. For this reason, even if the torque ripple corresponding to each of the plurality of winding groups is large, the torque ripple can be reduced by synthesizing the torque corresponding to each of the plurality of winding groups.

The above object and other objects, features and advantages of the present disclosure will become more apparent from the following detailed description with reference to the attached drawings. The drawing is
Fig. 1 is an overall configuration diagram of a control system of a rotating electrical machine, FIG. 2 is a diagram showing the spatial phase difference between the first winding group and the second winding group, FIG. 3 is a block diagram showing the processing of the control device; FIG. 4 is a diagram showing voltage vectors in the dq coordinate system; FIG. 5 is a time chart showing the operation mode (W = 120 degrees) of the switch, FIG. 6 is a time chart showing the operation mode of the switch (60 degrees <W <120 degrees), FIG. 7 is a time chart showing the operation mode (W = 60 degrees) of the switch, FIG. 8 is a time chart showing phase voltages etc. before and after the filter, FIG. 9 is a time chart showing the electrical angle before and after phase compensation, FIG. 10 is a diagram showing the relationship between the phase compensation amount and the electrical angular velocity, FIG. 11 is a diagram showing the effect of the present embodiment on angle estimation, FIG. 12 is a diagram showing the reduction effect of torque ripple, FIG. 13 is a diagram showing the reduction effect of the ripple of direct current, FIG. 14 is a diagram showing the noise reduction effect.

Hereinafter, an embodiment of a control device according to the present disclosure will be described with reference to the drawings. In the present embodiment, the control device is mounted on a vehicle equipped with an engine as a vehicle-mounted main device.

As shown in FIG. 1, the control system includes a rotating electrical machine 10. The rotary electric machine 10 is a synchronous machine having a multiphase multi-winding, specifically, a three-phase double winding. In the present embodiment, the rotary electric machine 10 is an ISG (Integrated Starter Generator) in which functions of a motor and a generator are integrated. The rotor 11 of the rotary electric machine 10 can transmit power to the crankshaft 20 a of the engine 20. In the present embodiment, the rotor 11 is mechanically connected to the crankshaft 20 a via, for example, a belt.

The rotor 11 is provided with a magnetic pole portion 12. In the present embodiment, since the rotary electric machine 10 is a winding field type, the magnetic pole portion 12 is a field winding. The first winding group 14 and the second winding group 15 are wound around the stator 13 of the rotary electric machine 10. The rotor 11 is made common to the first and

second winding groups

14 and 15. Each of the first winding group 14 and the second winding group 15 consists of three-phase windings having different neutral points. The first winding group 14 has U, V,

W phase windings

14U, 14V, 14W mutually offset by 120 ° in electrical angle, and the second winding group 15 is U offset from each other by 120 ° in electrical angle , V,

W phase windings

15U, 15V, 15W. In the present embodiment, as shown in FIG. 2, the spatial phase difference Δθ, which is an electrical angle between the first winding group 14 and the second winding group 15, is 30 °. That is, the electrical angle formed between the U-phase winding 14U of the first winding group 14 and the U-phase winding 15U of the second winding group 15 is 30 °. In the present embodiment, for convenience of explanation, it is assumed that the second winding group 15 is deviated from the first winding group 14 by the spatial phase difference Δθ on the advance side. In the present embodiment, the first winding group 14 and the second winding group 15 have the same configuration. Specifically, the number of turns of each phase winding 14U to 14W constituting first winding group 14 and the number of turns of each phase winding 15U to 15W constituting second winding group 15 are set equal. ing.

The control system includes a first inverter INV1, a second inverter INV2, and a DC power supply 21. The first winding group 14 is connected to the first inverter INV1, and the second winding group 15 is connected to the second inverter INV2. A common DC power supply 21 is connected to each of the first inverter INV1 and the second inverter INV2. The DC power supply 21 is, for example, a secondary battery.

The first inverter INV1 includes three series connected bodies of first U, V, W phase upper arm switches SUp1, SVp1, SWp1 and first U, V, W phase lower arm switches SUn1, SVn1, SWn1. The connection point of the series connection in the U, V, W phases is connected to the first end of the U, V,

W phase windings

14U, 14V, 14W. The second ends of the U, V,

W phase windings

14U, 14V, 14W are connected to one another at a neutral point. In the present embodiment, N-channel MOSFETs are used as the switches SUp1 to SWn1. The diodes DUp1, DVp1, DWp1, DUn1, DVn1, DWn1 are connected in anti-parallel to the switches SUp1, SVp1, SWp1, SUn1, SVn1, SWn1. Each of the diodes DUp1 to DWn1 may be a body diode of each of the switches SUp1 to SWn1. The switches SUp1 to SWn1 are not limited to N-channel MOSFETs, and may be, for example, IGBTs.

Similar to the first inverter INV1, the second inverter INV2 is a series connection of the second U, V, W-phase upper arm switches SUp2, SVp2, SWp2 and the second U, V, W-phase lower arm switches SUn2, SVn2, SWn2. It has three sets of bodies. The connection point of the series connection in the U, V, W phases is connected to the first end of the U, V,

W phase windings

15U, 15V, 15W. The second ends of the U, V,

W phase windings

15U, 15V, 15W are connected to each other at a neutral point. In the present embodiment, N-channel MOSFETs are used as the switches SUp2 to SWn2. The diodes DUp2, DVp2, DWp2, DUn2, DVn2, and DWn2 are connected in reverse parallel to the switches SUp2, SVp2, SWp2, SUn2, SVn2, and SWn2, respectively. The diodes DUp2-DWn2 may be body diodes of the switches SUp2-SWn2. The switches SUp2 to SWn2 are not limited to N-channel MOSFETs, and may be, for example, IGBTs.

The positive electrode terminal of the DC power supply 21 is connected to the drain which is the high potential side terminal of the upper arm switch of each of the first and second inverters INV1 and INV2. The negative terminal of the DC power supply 21 is connected to the source which is the low potential side terminal of each lower arm switch.

The first and second inverters INV1 and INV2 convert a DC voltage output from the DC power supply 21 into an AC voltage during powering drive for driving the rotary electric machine 10 as a motor, to convert the first and second winding groups 14, It has a function to apply to 15. As a result, for example, the engine 20 can be started, or torque assist can be performed to transmit the generated torque of the electric motor to the drive wheels when the vehicle is traveling. The first and second inverters INV1 and INV2 convert alternating current voltages output from the first and second winding

groups

14 and 15 into direct current voltage during regenerative drive for driving the rotary electric machine 10 as a generator. It has a function of applying to the DC power supply 21. Thereby, for example, the DC power supply 21 can be charged.

The control system comprises a controller 30. The control device 30 includes a CPU and a memory, and the CPU executes a program stored in the memory. Control device 30 operates the switches constituting first inverter INV1 and second inverter INV2 in order to control the control amount of rotary electric machine 10 to the command value. In the present embodiment, the control amount is torque, and the command value is command torque Trq *. The functions provided by the control device 30 can be provided, for example, by software stored in a tangible memory device and a computer that executes the software, hardware, or a combination thereof.

The control device 30 performs position sensorless control that does not use the detection value of the angle detector that directly detects the rotation angle of the rotary electric machine 10. In order to perform position sensorless control, the control system is provided with a configuration for detecting the fundamental wave component of the induced voltage generated in the winding. Specifically, the control system comprises a series connection of a first resistor 22a and a second resistor 22b. The series connected body of the resistors 22 a and 22 b is connected in parallel to the DC power supply 21. In the present embodiment, the resistance values of the resistors 22a and 22b are the same. The output voltage VDC of the DC power supply 21 divided by the resistors 22 a and 22 b is input to the control device 30. The voltage at the first end of U-phase winding 14U is also input to control device 30. Control device 30 determines the U-phase voltage in first winding group 14 based on the voltage at the first end side of U-phase winding 14 U based on the voltage division value “VDC / 2” by each of the resistors 22 a and 22 b. Get VU1. The acquired phase voltage is not limited to the phase voltage of the U-phase winding 14U of the first winding group 14.

FIG. 3 is a block diagram of the torque control process performed by the control device 30.

Based on command torque Trq *, setting unit 31 sets voltage amplitude Vamp, which is the magnitude of voltage vector Vn, and voltage phase δ, which is the phase of voltage vector Vn. The voltage vector Vn, as shown in FIG. 4, is a vector consisting of d-axis voltage and q-axis voltage in the dq coordinate system. FIG. 4 shows that the positive direction of the q axis is a reference, and the counterclockwise direction from this reference is the positive direction (advance side) of the voltage phase δ. The lead angle of the d axis of the dq coordinate system corresponding to each of the winding

groups

14 and 15 is defined based on the U-phase windings 14U and 15U of each of the winding

groups

14 and 15. The setting unit 31 may set the voltage amplitude Vamp and the voltage phase δ based on map information in which the command torque Trq * is related to the voltage amplitude Vamp and the voltage phase δ.

The pulse width adjustment unit 32 adjusts the pulse width W indicating the length of the conduction period based on the voltage amplitude Vamp. The pulse width W is made larger as the voltage amplitude Vamp is larger. In the present embodiment, the pulse width W is set to 120 degrees or less. Further, in the present embodiment, when the rotary electric machine 10 is driven as an electric motor, the pulse width W is set to be greater than 60 degrees and equal to or less than 120 degrees.

As shown in FIG. 5, the first operation unit 33 is configured as shown in FIG. 5 based on the pulse width W, the voltage phase δ, and the estimated electrical angle θest corresponding to rotational position information output from the phase compensation unit 38 described later. 1) Generate and output operation signals of the switches SUp to SWn1 of the inverter INV1. In FIGS. 5A to 5C, 1 indicates that the upper arm switch is turned on and the lower arm switch is turned off. 0 indicates a dead time in which both the upper and lower arm switches are turned off. -1 indicates that the upper arm switch is turned off and the lower arm switch is turned on. For example, 1 in FIG. 5A indicates that the first U-phase upper arm switch SUp1 is turned on and the first U-phase lower arm switch SUn1 is turned off.

FIG. 5 shows the case where the pulse width W is set to 120 degrees, and FIG. 6 shows the case where the pulse width W is set to a value larger than 60 degrees and smaller than 120 degrees. FIGS. 6 (a) to 6 (c) correspond to FIGS. 5 (a) to 5 (c).

As shown in FIGS. 5 and 6, the switching timing to the on operation of the upper arm switch of each of the U, V, and W phases is shifted by 120 degrees. Further, the switching timing of the lower arm switch of each of the U, V, and W phases to the on operation is also shifted by 120 degrees. It is assumed that the ON operation periods of the upper arm switches of the U, V, and W phases do not overlap due to such timing deviation and that the pulse width W is made larger than 60 degrees and smaller than 120 degrees. The first condition is imposed, which is the condition of Further, a second condition is imposed, which is a condition that the ON operation periods of the lower arm switches of the U, V, and W phases do not overlap.

As shown in FIG. 5, when the pulse width W is set to 120 degrees, the non-conducting periods of the phase windings 14U to 14W in the first winding group 14 do not overlap with each other. The non-energization period of each phase is 60 degrees in electrical angle.

In the present embodiment, when the rotary electric machine 10 is driven as an electric motor, the pulse width W is set to a value larger than 60 degrees. This setting is to prevent the occurrence of a situation where power can not be supplied from the DC power supply 21 to the inverters INV1 and INV2. FIG. 7 shows the case where the pulse width W is set to 60 degrees. FIGS. 7A to 7C correspond to FIGS. 5A to 5C. As shown in FIG. 7, when the pulse width W is 60 degrees, the upper arm switch and the lower arm switch of different phases are not simultaneously turned on. Therefore, power can not be supplied from the DC power supply 21 to the first inverter INV1.

Returning to the explanation of FIG. 3, the second operation unit 34 switches the respective switches SUp2 to SWn2 of the second inverter INV2 based on the pulse width W, the voltage phase δ, and the output value “θest + Δθ” of the addition unit 35 described later. Generate and output the operation signal of The operation modes of the switches SUp2 to SWn2 of the second inverter INV2 are obtained by advancing the operation modes shown in FIGS. 5 and 6 by the space phase difference Δθ.

Subsequently, a method of calculating the estimated electrical angle θest will be described.

The filter unit 36 performs low-pass filter processing on the acquired phase voltage VU1 to extract the fundamental wave component of the induced voltage of the U-phase winding 14U. Hereinafter, the extracted fundamental wave component is referred to as a post-filter voltage VF. In FIG. 8A, the fundamental wave component EU1 of the actual induced voltage of the U-phase winding 14U is indicated by a broken line, and the acquired phase voltage VU1 is indicated by a solid line. In FIG. 8A, the period from time t2 to t3 is a period in which the first U-phase upper arm switch SUp1 is turned on and the first U-phase lower arm switch SUn1 is turned off. The phase voltage VU1 in this period is clamped at a value corresponding to the voltage on the positive electrode side of the DC power supply 21.

A period from time t4 to t5 is a period in which the first U-phase upper arm switch SUp1 is turned off and the first U-phase lower arm switch SUn1 is turned on. Phase voltage VU1 in this period is clamped to a value corresponding to the voltage on the negative electrode side of DC power supply 21.

The period from time t1 to t2 and t3 to t4 is a dead time. In the dead time, two noises are superimposed on the phase voltage VU1. These noises are the switching noise corresponding to the phase other than the U phase in the first winding group 14 and the switching noise corresponding to any phase in the second winding group 15. Since the spatial phase difference Δθ is 30 °, for example, the generation interval of these noises is 30 ° in electrical angle. These noises can be removed by the low pass filter processing of the filter unit 36.

Returning to the description of FIG. 3, the estimation unit 37 calculates the uncompensated electrical angle θp based on the filtered voltage VF output from the filter unit 36. Specifically, as shown in FIG. 8B, the estimation unit 37 first compares the after-filter voltage VF with the threshold, and calculates the timing at which the after-filter voltage VF crosses the threshold. In the present embodiment, the threshold is set to zero. Therefore, the timing at which the filtered voltage VF crosses the threshold is the zero cross timing. Then, the estimation unit 37 calculates the precompensation electrical angle θp, as shown in FIG. 9A, based on the calculated zero cross timing. The electrical angle can be estimated based on the zero cross timing because, for example, the zero cross timing of the fundamental wave component EU1 of the actual induced voltage can be used as a reference timing for estimating the electrical angle. FIG. 9 shows the transition of the pre-compensation electrical angle θp when the electrical angular velocity of the rotary electric machine 10 is constant.

The estimation unit 37 further calculates the electric angular velocity ωest of the rotary electric machine 10 based on the calculated time interval of the zero cross timing.

The phase compensation unit 38 calculates the estimated electrical angle θest by correcting the precompensation electrical angle θp on the phase advancing side. The correction on the phase advancing side is performed by low-pass filter processing, and as shown in FIG. 8B, the phase of the filtered voltage VF is delayed with respect to the fundamental wave component EU1 of the actual induced voltage. It is for. The phase compensation can improve the estimation accuracy of the electrical angle.

The phase compensation unit 38 calculates the phase compensation value β (<0) shown in FIG. 10 based on the electrical angular velocity ωest, and adds the calculated phase compensation value β to the pre-compensation electrical angle θp to estimate the electrical angle Calculate θest. The phase compensation unit 38 may calculate the phase compensation value β based on the map information in which the electrical angular velocity ωest and the phase compensation value β are related. Thus, the phase delay of the precompensation electrical angle θp can be compensated with a simple configuration.

The addition unit 35 adds the spatial phase difference Δθ to the estimated electrical angle θest output from the phase compensation unit 38 and outputs the result.

Subsequently, the effects of the present embodiment will be described using FIGS. 11 to 14.

First, the improvement effect of the estimation accuracy of the electrical angle will be described with reference to FIG. FIG. 11A shows the transition of the U-phase voltage VU1 and the after-filter voltage VF of this embodiment, and FIG. 11B shows the transition of the U-phase voltage VU1 and the after-filter voltage VF of the comparative example. The comparative example of FIG. 11B has a configuration in which the upper and lower arm switches are alternately turned on during the on operation period of the upper arm switch as described in Patent Document 1 above.

In the present embodiment, since the symmetry of the phase voltage VU1 is secured to some extent with respect to 0 V, the filtered voltage VF is not offset from 0 V. Therefore, the estimation accuracy of the electrical angle can be improved. On the other hand, in the comparative example, the symmetry of the phase voltage VU1 is not ensured with respect to 0 V, so the filtered voltage VF is offset from 0 V by a predetermined amount ΔV. As a result, the reference timing for estimating the electrical angle can not be properly grasped, and the estimation accuracy of the electrical angle decreases. In the comparative example, in order to prevent a decrease in the estimation accuracy of the electrical angle, the reference voltage in acquiring phase voltage VU1 is replaced with the divided voltage value “VDC / 2” of the output voltage of DC power supply 21 to be virtual. It is also conceivable to use a neutral point voltage. However, in this case, the number of components increases and the cost of the control system increases.

Then, the reduction effect of a torque ripple is demonstrated using FIG. 11A shows the transition of the torque Trq1 of the rotary electric machine 10 corresponding to the first winding group 14, and FIG. 11B shows the torque Trq2 of the rotary electric machine 10 corresponding to the second winding group 15. Show the transition. FIG. 11C shows transition of combined torque Ttotal which is a total value of each of the torques Trq1 and Trq2.

When the pulse width W is smaller than 120, a non-energization period for the windings appears in each of the first and second winding

groups

14 and 15. In this case, sixth torque ripple occurs in each of the torques Trq1 and Trq2. However, even if the torque ripple corresponding to each of the first and second winding

groups

14 and 15 is large, the torque ripple is reduced as shown in FIG. 12C by combining the respective torques Trq1 and Trq2. can do. In particular, in the present embodiment, setting the spatial phase difference Δθ to 30 degrees further improves the reduction effect of the torque ripple.

The space phase difference Δθ is not limited to 30 degrees, and the torque ripple reduction effect can be obtained even when it is set to a value close to 30 degrees.

Subsequently, the ripple reduction effect of direct current will be described with reference to FIG. FIG. 13 (a) shows the transition of the first DC current IDC1 flowing between the DC power supply 21 and the first inverter INV1, and FIG. 13 (b) shows the transition between the DC power supply 21 and the second inverter INV2. The transition of 2nd DC current IDC2 is shown. FIG. 13C shows the transition of the combined current Itotal which is the total value of the direct current IDC1 and IDC2.

According to the present embodiment, it is possible to reduce the ripple of the direct current as well as the torque ripple. Therefore, the capacity of the smoothing capacitor provided between each of the inverters INV1 and INV2 and the DC power supply 21 and connected in parallel to the DC power supply 21 can be reduced, and the size of the smoothing capacitor can be reduced. In particular, in the present embodiment, the smoothing capacitor is not included in the control system by reducing the ripple of the direct current.

Subsequently, the reduction effect of the electromagnetic noise will be described with reference to FIG. In addition, the comparative example shown in FIG. 14 is the same as the comparative example of FIG.11 (b).

In the present embodiment, in order to adjust the torque of the rotary electric machine 10, the pulse width W is adjusted. Therefore, the electromagnetic noise can be reduced more than in the comparative example. In addition, the switching loss generated in each of the inverters INV1 and INV2 can be reduced as compared with the comparative example.

<Other Embodiments>
The above embodiment may be modified as follows.

The reference voltage for acquiring the phase voltage is not limited to the voltage division value "VDC / 2" of each of the resistors 22a and 22b, and may be, for example, a ground voltage (0 V) which is a voltage on the negative electrode side of the DC power supply 21. It may be.

The threshold used by the estimation unit 37 is not limited to zero, and may be a value other than zero.

The method of estimating the electrical angle is not limited to that using a low pass filter. For example, the electrical angle may be estimated based on the comparison between the phase voltage and the threshold in the non-energized period of the winding. Further, the electrical angle is not limited to one estimated by position sensorless control. For example, an electrical angle detected by an angle detector such as a resolver may be used for torque control.

The rotating electric machine is not limited to the one having two winding groups, and may have three or more winding groups. In this case, assuming that the number of winding groups is N, the spatial phase difference Δθ of each winding group may be “Δθ = 60 degrees / N”. For example, when the number of winding groups is three, the spatial phase difference Δθ between the first to third winding groups is set to 20 degrees.

The control amount of the rotating electrical machine is not limited to the torque, and may be, for example, a rotational speed.

-As a rotary electric machine, the thing of multiple phases other than three phases may be used. The rotating electrical machine is not limited to the winding field type, and may be, for example, a permanent magnet field type. In this case, the magnetic pole portion is a permanent magnet.

Although the present disclosure has been described based on the examples, it is understood that the present disclosure is not limited to the examples and structures. The present disclosure also includes various modifications and variations within the equivalent range. In addition, various combinations and forms, and further, other combinations and forms including only one element, or more or less than these elements are also within the scope and the scope of the present disclosure.

Claims

A rotating electric machine (10) having multi-phase winding groups (14, 15);
A series connection of upper arm switches (SUp1 to SWp2) and lower arm switches (SUn1 to SWn2) is provided, and the voltage is applied to the winding group by alternately turning on the upper arm switch and the lower arm switch. In a control device (30) of a rotating electrical machine applied to a system including a power conversion circuit (INV1, INV2) that applies
An adjusting unit (32) for adjusting a pulse width which is an on operation period of each of the upper arm switch and the lower arm switch in one electrical angle cycle of the rotating electrical machine;
The first condition that the ON operation period of the upper arm switch corresponding to each phase is not overlapped, and the second condition that the ON operation period of the lower arm switch corresponding to each phase is not overlapped, 1 The upper arm switch and the lower arm switch are set to 1 each in one electrical angle cycle in order to make the on-operation period of each of the upper arm switch and the lower arm switch in the electrical angle cycle be the pulse width adjusted by the adjustment unit. A control device for a rotating electrical machine, comprising: an operation unit (33, 34) which is turned on each time.
The rotating electric machine has a plurality of winding groups,
The power conversion circuit applies a voltage to each of the plurality of winding groups,
The electrical angles that each of the plurality of winding groups make with each other are offset;
The operation unit imposes the first condition and the second condition in each of the plurality of winding groups, and adjusts the on operation period of each of the upper arm switch and the lower arm switch in one electrical angle cycle. The control device for a rotating electrical machine according to claim 1, wherein the upper arm switch and the lower arm switch are each turned on once in one electrical angle cycle in order to obtain the pulse width adjusted by the unit.
The winding group is of three phases,
The control device for a rotating electrical machine according to claim 2, wherein the adjustment unit adjusts the pulse width to 120 degrees or less in electrical angle.
The control device for a rotating electrical machine according to claim 3, wherein, when the rotating electrical machine is driven as a motor, the adjusting unit adjusts the pulse width to be greater than 60 degrees and 120 degrees or less in electrical angle.
The estimation unit (37) for estimating the rotational position information of the rotor of the rotating electrical machine based on comparison between the phase voltage generated in the winding (14U) forming the winding group and the threshold value. The control device of the rotary electric machine according to any one of the above.
A filter unit (36) for extracting a fundamental wave component of the induced voltage generated in the winding by filtering the phase voltage generated in the winding;
The control device of a rotating electrical machine according to claim 5, wherein the estimation unit estimates the rotational position information based on comparison between the fundamental wave component extracted by the filter unit and the threshold value.
The compensation unit (38) compensates for the phase delay of the fundamental wave component extracted by the filter unit with respect to the fundamental wave component of the induced voltage actually generated in the winding.
The control device for a rotating electrical machine according to claim 6, wherein the estimation unit estimates the rotational position information based on comparison between the fundamental wave component compensated by the compensation unit and the threshold value.