WO2018077028A1 - Signal processing method and apparatus - Google Patents

Signal processing method and apparatus Download PDF

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WO2018077028A1
WO2018077028A1 PCT/CN2017/105601 CN2017105601W WO2018077028A1 WO 2018077028 A1 WO2018077028 A1 WO 2018077028A1 CN 2017105601 W CN2017105601 W CN 2017105601W WO 2018077028 A1 WO2018077028 A1 WO 2018077028A1
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training sequence
received signal
signal processing
signal
processing method
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PCT/CN2017/105601
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French (fr)
Chinese (zh)
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刘若鹏
季春霖
张莎莎
吕长伟
方超
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深圳超级数据链技术有限公司
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Priority claimed from CN201610926051.6A external-priority patent/CN107979547A/en
Priority claimed from CN201610927722.0A external-priority patent/CN107979549A/en
Priority claimed from CN201610926152.3A external-priority patent/CN107979553B/en
Priority claimed from CN201610926428.8A external-priority patent/CN107979556A/en
Priority claimed from CN201610926320.9A external-priority patent/CN107979555A/en
Priority claimed from CN201610926426.9A external-priority patent/CN107979548A/en
Application filed by 深圳超级数据链技术有限公司 filed Critical 深圳超级数据链技术有限公司
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    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems

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Abstract

The present invention provides a signal processing method, comprising: pre-processing a received signal, which comprises a complete complementary orthogonal dual code-based training sequence and data, the pre-processing process comprising pre-processing the received signal using the complete complementary orthogonal dual code-based training sequence.

Description

信号处理方法及装置Signal processing method and device 技术领域Technical field
本发明涉及无线通信系统,尤其涉及信号处理方法及装置。The present invention relates to a wireless communication system, and more particularly to a signal processing method and apparatus.
背景技术Background technique
无线通信网络被广泛部署以提供诸如语音、视频、分组数据、消息接发、广播等各种通信服务。这些无线网络可以是能够通过共享可用的网络资源来支持多个用户的多址网络。这类多址网络的示例包括码分多址(CDMA)网络、时分多址(TDMA)网络、频分多址(FDMA)网络、正交FDMA(OFDMA)网络、以及单载波FDMA(SC-FDMA)网络。Wireless communication networks are widely deployed to provide various communication services such as voice, video, packet data, messaging, broadcast, and the like. These wireless networks may be multiple-access networks capable of supporting multiple users by sharing available network resources. Examples of such multiple access networks include Code Division Multiple Access (CDMA) networks, Time Division Multiple Access (TDMA) networks, Frequency Division Multiple Access (FDMA) networks, Orthogonal FDMA (OFDMA) networks, and Single Carrier FDMA (SC-FDMA). )The internet.
随着全球移动通信不断增强的需求,无线通信的频率资源愈趋紧张。因此,除了基于TDM(时分复用)、FDM(频分复用)的上述传统高频谱利用率的无线通信系统之外,还提出了对于频谱具有更高利用率的更激进的通信方案。With the ever-increasing demand for global mobile communications, the frequency resources of wireless communications are becoming more and more tense. Therefore, in addition to the above-described conventional high spectrum utilization wireless communication system based on TDM (Time Division Multiplexing) and FDM (Frequency Division Multiplexing), a more aggressive communication scheme with higher utilization rate for the spectrum has been proposed.
重叠时分复用(Overlapped Time Division Multiplexing,OvTDM)系统正是这样一种提高系统频谱效率的方案。在OvTDM系统中,符号之间不但不需要相互隔离,而且可以有很强的相互重叠。换言之,OvTDM系统通过人为地引入符号之间的重叠,利用多个符号在时域并行传输数据序列,大幅提高了频谱利用率。The Overlapped Time Division Multiplexing (OvTDM) system is such a solution to improve the spectrum efficiency of the system. In the OvTDM system, not only do not need to be isolated from each other, but they can also overlap each other. In other words, the OvTDM system significantly increases the spectrum utilization by artificially introducing the overlap between symbols and using multiple symbols to transmit data sequences in parallel in the time domain.
重叠频分复用(Overlapped Frequency Division Multiplexing,OvFDM)系统是另外一种提高系统频谱效率的方案。在OvFDM系统中,子载波频带之间可以有比正交频分复用OFDM更强的重叠。通过频域内各子频带之间更高的重叠程度,在OFDM系统的基础上进一步提高了频谱利用率。Overlapped Frequency Division Multiplexing (OvFDM) system is another solution to improve the spectrum efficiency of the system. In an OvFDM system, there may be a stronger overlap between subcarrier bands than Orthogonal Frequency Division Multiplexing (OFDM). The spectrum utilization is further improved on the basis of the OFDM system by the higher degree of overlap between the sub-bands in the frequency domain.
类似的系统还有重叠空分复用(Overlapped Spatial Division Multiplexing,OvSDM)系统、重叠混合复用(Overlapped Hybrid Division Multiplexing,OvHDM)系统、重叠码分复用(Overlapped Code Division Multiplexing,OvCDM)系统。这些系统可统一用OvXDM表示,其中X可代表时间T、频率F、空间S、混合H或码分C。Similar systems include an Overlapped Spatial Division Multiplexing (OvSDM) system, an Overlapped Hybrid Division Multiplexing (OvHDM) system, and an Overlapped Code Division Multiplexing (OvCDM) system. These systems can be uniformly represented by OvXDM, where X can represent time T, frequency F, space S, mixed H, or code division C.
尽管上述OvXDM系统具有相应的接收解调方案来排除信号在时域、频域等的重叠所带来的干扰,但是频谱利用率的大幅提高仍然对信号的接收提出了更高要求。Although the above OvXDM system has a corresponding receiving demodulation scheme to eliminate interference caused by overlapping of signals in the time domain, the frequency domain, etc., the substantial increase in spectrum utilization still places higher demands on signal reception.
因此,OvXDM系统需要更高性能的网络接入方案。Therefore, OvXDM systems require higher performance network access solutions.
发明内容Summary of the invention
以下给出一个或多个方面的简要概述以提供对这些方面的基本理解。此概述不是所有构想到的方面的详尽综览,并且既非旨在指认出所有方面的关键性或决定性要素亦非试图界定任何或所有方面的范围。其唯一的目的是要以简化形式给 出一个或多个方面的一些概念以为稍后给出的更加详细的描述之序。A brief overview of one or more aspects is provided below to provide a basic understanding of these aspects. This summary is not an extensive overview of all aspects that are conceived, and is not intended to identify key or critical elements in all aspects. Its sole purpose is to give it in a simplified form. Some concepts in one or more aspects are in the order of a more detailed description that will be given later.
根据本发明的一方面,提供了一种信号处理方法,包括:对接收信号执行预处理,该接收信号包括基于完备互补正交对偶码的训练序列,该执行预处理包括采用该基于完备互补正交对偶码的训练序列对该接收信号执行预处理。According to an aspect of the present invention, a signal processing method is provided, comprising: performing pre-processing on a received signal, the received signal comprising a training sequence based on a complete complementary orthogonal dual code, the performing pre-processing comprising employing the complete complement-based positive The training sequence of the dual code performs preprocessing on the received signal.
根据本发明的另一方面,提供了一种信号处理装置,包括:According to another aspect of the present invention, a signal processing apparatus is provided, comprising:
预处理单元,用于对接收信号执行预处理,该接收信号包括基于完备互补正交对偶码的训练序列,该预处理单元采用该基于完备互补正交对偶码的训练序列对该接收信号执行预处理。a pre-processing unit, configured to perform pre-processing on the received signal, where the received signal includes a training sequence based on a complete complementary orthogonal dual code, and the pre-processing unit performs the pre-preparation on the received signal by using the training sequence based on the complete complementary orthogonal dual code deal with.
附图说明DRAWINGS
图1示出了OvXDM系统的卷积编码等效模型;Figure 1 shows a convolutional code equivalent model of the OvXDM system;
图2示出了K路复用波形的排列;Figure 2 shows an arrangement of K-way multiplexed waveforms;
图3示出了K=3的OvTDM系统的输入-输出关系的树图;Figure 3 shows a tree diagram of the input-output relationship of an OvTDM system with K = 3;
图4示出了节点状态转移关系图;Figure 4 shows a node state transition relationship diagram;
图5示出了K=3的格状图;Figure 5 shows a trellis diagram of K = 3;
图6示出了OvTDM系统的发射端调制模块的框图;Figure 6 shows a block diagram of a transmitter modulation module of an OvTDM system;
图7示出了OvTDM系统的接收端的信号预处理模块的框图;Figure 7 shows a block diagram of a signal pre-processing module at the receiving end of the OvTDM system;
图8示出了OvTDM系统的接收端序列检测模块的框图;Figure 8 is a block diagram showing the receiving end sequence detecting module of the OvTDM system;
图9示出了M序列的自相关特性;Figure 9 shows the autocorrelation properties of the M sequence;
图10示出了完备互补正交对偶码的自相关特性;Figure 10 shows the autocorrelation properties of a complete complementary orthogonal dual code;
图11示出了根据本发明的一实施例的载波同步装置的框图;Figure 11 is a block diagram showing a carrier synchronization apparatus according to an embodiment of the present invention;
图12示出了根据本发明的一实施例的载波同步方法的流程图;FIG. 12 is a flowchart showing a carrier synchronization method according to an embodiment of the present invention; FIG.
图13示出了根据本发明的一实施例的信道估计装置的框图;Figure 13 shows a block diagram of a channel estimation apparatus in accordance with an embodiment of the present invention;
图14示出了根据本发明的一实施例的信道估计方法的流程图;FIG. 14 shows a flowchart of a channel estimation method according to an embodiment of the present invention; FIG.
图15示出了等频宽系统的功率谱密度和频宽关系图;Figure 15 is a graph showing the power spectral density and bandwidth of an equal bandwidth system;
图16示出了根据本发明的一方面的训练序列和数据的频宽及功率谱密度关系图;以及16 shows a plot of bandwidth and power spectral density for a training sequence and data in accordance with an aspect of the present invention;
图17示出了根据本发明的一方面的两个载波信号同时发送数据时的频谱示意图。Figure 17 is a diagram showing the frequency spectrum when two carrier signals are simultaneously transmitted according to an aspect of the present invention.
具体实施方式detailed description
以下结合附图和具体实施例对本发明作详细描述。注意,以下结合附图和具体实施例描述的诸方面仅是示例性的,而不应被理解为对本发明的保护范围进行任何限制。 The invention is described in detail below with reference to the drawings and specific embodiments. It is to be noted that the aspects described below in conjunction with the drawings and the specific embodiments are merely exemplary and are not to be construed as limiting the scope of the invention.
除了应用在OvXDM系统中,本文中所描述的诸技术也可广泛应用于实际移动通信系统中,如TD-LTE、TD-SCDMA等系统,也可广泛应用于卫星通信、微波视距通信、散射通信、大气层光通信、红外通信与水生通信等任何无线通信系统中。术语“网络”和“系统”常被可互换地使用。In addition to being used in the OvXDM system, the techniques described in this paper can also be widely applied to practical mobile communication systems, such as TD-LTE, TD-SCDMA, etc., and can also be widely applied to satellite communication, microwave line-of-sight communication, and scattering. In any wireless communication system such as communication, atmospheric optical communication, infrared communication, and aquatic communication. The terms "network" and "system" are often used interchangeably.
移动通信的不断发展以及新业务的层出不穷对数据传输速率提出了越来越高的要求,而移动通信的频率资源却十分有限,如何利用有限的频率资源实现数据的高速传输成为当今移动通信技术面临的一个重要问题The continuous development of mobile communication and the emergence of new services have put forward higher and higher requirements for data transmission rate, while the frequency resources of mobile communication are very limited. How to realize the high-speed transmission of data by using limited frequency resources has become the face of today's mobile communication technology. An important issue
上述OvXDM系统正是这种可以大幅提高频谱利用率的解决方案。图1示出了OvXDM系统的卷积编码等效模型。The above OvXDM system is the solution that can greatly improve the spectrum utilization. Figure 1 shows the convolutional code equivalent model of the OvXDM system.
下面简要介绍作为OvXDM系统的一个示例的OvTDM系统的发送和接收过程。The transmission and reception process of the OvTDM system as an example of the OvXDM system is briefly described below.
OvTDM系统利用多个符号在时间域并行传输数据序列。在发射端形成多个符号在时间域上相互重叠的发射信号,在接收端根据传输数据序列与传输数据序列时间波形之间的一一对应关系,对接收信号进行时间域内的按数据序列检测。OvTDM系统积极利用这些重叠使之产生编码约束关系,从而大幅度提高了系统的频谱效率。The OvTDM system uses multiple symbols to transmit data sequences in parallel in the time domain. A transmitting signal in which a plurality of symbols overlap each other in the time domain is formed at the transmitting end, and the received signal is detected by the data sequence in the time domain according to a one-to-one correspondence between the transmitted data sequence and the time waveform of the transmitted data sequence. The OvTDM system actively exploits these overlaps to create coding constraints, which greatly increases the spectral efficiency of the system.
图2示出了K路复用波形的排列。OvTDM系统的树图表示是一种很形象的表示OvTDM系统输入-输出关系的方式。图3示出了K=3的OvTDM系统的输入-输出关系的树图。图中用向上的树枝表示输入比特为1,而向下的树枝则表示输入比特为-1,而对应的编码输出则表示在各树枝的上方。从图中可见,输入与输出序列之间完全一一对应。绝没有某个输入序列与两个或两个以上的输出序列相对应,反之亦然。因此,符号重叠并未破坏时域内输入输出序列之间的一一对应关系,于是若在时域内按序列进行检测就不可能出现不可再减的差错概率。Figure 2 shows the arrangement of the K-way multiplexed waveforms. The tree diagram representation of the OvTDM system is a very visual representation of the input-output relationship of the OvTDM system. Figure 3 shows a tree diagram of the input-output relationship of an OvTDM system with K = 3. In the figure, the upward branch indicates that the input bit is 1, while the downward branch indicates that the input bit is -1, and the corresponding encoded output is above the branches. As can be seen from the figure, there is a complete one-to-one correspondence between the input and output sequences. There is absolutely no input sequence that corresponds to two or more output sequences, and vice versa. Therefore, the symbol overlap does not destroy the one-to-one correspondence between the input and output sequences in the time domain, so if the detection is performed in sequence in the time domain, it is impossible to have an error probability that cannot be reduced.
从图3中可以发现,在第三枝以后该树图就变为重复的了,因为凡是从标记为a的节点辐射出的树枝都有同样的输出,该结论对节点b、c、d也同样正确。它们不外乎是如下几种可能(见图4)。从图中可以看出从节点a只能转移到(经输入+1)节点a及(经输入-1)节点b,同时b只能到(输入+1)c及(输入-1)d,c只能到(输入+1)a及(输入-1)b,d只能到(输入+1)c及(输入-1)d。产生这种现象的原因很简单,因为只有相邻K(具体到本例是3)个符号才会形成相互干扰。所以当第K位数据输入到信道时,最早来的第1位数据已经移出最右边的一个移位单元了。因此信道的输出除了取决于现时刻数据的输入,只决定于前K-1个数据的输入。一般来说,对于M=2Q,即Q维二元数据输入,只要前K-1个Q维二元数据相同,它们对应的输出就相同。因此,图3中(Q=1)在第三个支路后,凡是标记为a的节点就可以合并 在一起,同样b、c及d节点也可以合并在一起,这样就形成一个折叠的树图——格状(Trellis)图,参见图5。It can be seen from Fig. 3 that the tree map becomes duplicated after the third branch, because all the branches radiated from the node marked a have the same output, and the conclusion is also for nodes b, c, and d. The same is true. They are nothing more than the following possibilities (see Figure 4). It can be seen from the figure that slave node a can only be transferred to (via input +1) node a and (via input -1) node b, while b can only go to (input +1)c and (input-1)d, c can only go to (input +1) a and (input -1) b, d can only go to (input +1)c and (input-1)d. The reason for this phenomenon is very simple, because only adjacent K (specifically 3 in this case) will form mutual interference. Therefore, when the K-th bit data is input to the channel, the earliest first bit data has been shifted out of the rightmost shift unit. Therefore, the output of the channel depends only on the input of the current time data, and is determined only by the input of the first K-1 data. In general, for M=2Q, that is, Q-dimensional binary data input, as long as the first K-1 Q-dimensional binary data are the same, their corresponding outputs are the same. Therefore, in Figure 3 (Q = 1) after the third branch, all nodes marked a can be merged. Together, the same b, c, and d nodes can also be merged together, thus forming a folded tree diagram, the Trellis diagram, see Figure 5.
图6示出了OvTDM系统的发射端调制模块的框图。发送端调制模块600可包括数字波形发生单元610、移位寄存单元620、乘法单元630及加法单元640。Figure 6 shows a block diagram of the transmit modulation module of the OvTDM system. The transmitting end modulation module 600 may include a digital waveform generating unit 610, a shift register unit 620, a multiplying unit 630, and an adding unit 640.
首先,由数字波形发生单元610以数字方式设计生成发送信号的第一个调制信号包络波形h(t),移位寄存单元620将该包络波形h(t)进行特定时间移位,形成其它各个时刻调制信号的包络波形h(t-i×ΔT),乘法单元630将所要发送的并行的符号xi与相应时刻的包络波形h(t-i×ΔT)相乘,得到各个时刻经调制后的待发送信号波形xih(t-i×ΔT)。加法单元640将所形成的各个待发送波形进行叠加,形成发射信号波形。First, the first modulated signal envelope waveform h(t) of the generated signal is digitally designed by the digital waveform generating unit 610, and the shift register unit 620 shifts the envelope waveform h(t) for a specific time to form The envelope waveform h (ti × ΔT) of the modulated signal at each other time, the multiplication unit 630 multiplies the parallel symbol x i to be transmitted with the envelope waveform h (ti × ΔT) at the corresponding time, and obtains the modulated time at each time. The waveform of the signal to be transmitted x i h(ti × ΔT). The addition unit 640 superimposes the formed waveforms to be transmitted to form a transmission signal waveform.
OvTDM系统的接收端主要分为信号预处理模块700和序列检测模块800。图7示出了OvTDM系统的接收端的信号预处理模块700的框图。信号预处理模块用于辅助形成每一帧内的同步接收数字信号序列,如图所示,该信号预处理模块可包括同步单元710、信道估计单元720、和数字化处理单元730。The receiving end of the OvTDM system is mainly divided into a signal pre-processing module 700 and a sequence detecting module 800. Figure 7 shows a block diagram of a signal pre-processing module 700 at the receiving end of the OvTDM system. The signal pre-processing module is operative to assist in forming a sequence of synchronized received digital signals within each frame. As shown, the signal pre-processing module can include a synchronization unit 710, a channel estimation unit 720, and a digitization processing unit 730.
同步单元710用于对接收信号在时域形成符号同步,以与系统保持同步状态,主要包括定时同步和载波同步。同步完成后信道估计单元720对接收信号做信道估计,以用于估计实际传输信道的参数。数字化处理单元730用于对每一帧内的接收信号进行数字化处理,从而形成适合序列检测部分进行序列检测的接收数字信号序列。The synchronization unit 710 is configured to form symbol synchronization in the time domain for the received signal to maintain a synchronization state with the system, mainly including timing synchronization and carrier synchronization. After synchronization is completed, channel estimation unit 720 performs channel estimation on the received signal for estimating parameters of the actual transmission channel. The digitization processing unit 730 is configured to digitize the received signal in each frame to form a received digital signal sequence suitable for sequence detection by the sequence detecting portion.
在预处理之后,可在序列检测模块800内对接收信号进行序列检测,对接收到的波形按照波形发送时间间隔切割并按照一定的译码算法对切割后的波形进行译码。图8示出了OvTDM系统的接收端序列检测模块的框图。如图所示,序列检测模块800可包括分析存储单元810、比较单元820、以及保留路径存储单元和欧氏距离存储单元830。在检测过程中,分析存储单元作出OvTDM系统的复数卷积编码模型及格状图,并列出OvTDM系统的全部状态,并存储。比较单元根据分析存储单元中的格状图,搜索出与接收数字信号最小欧氏距离的路径,而保留路径存储单元和欧氏距离存储单元则分别用于存储比较单元输出的保留路径和欧氏距离或加权欧氏距离。保留路径存储单元和欧氏距离存储单元需要为每一个稳定状态各准备一个。保留路径存储单元长度可以优选为4K~5K。欧氏距离存储单元优选为只存储相对距离。After the pre-processing, the received signal may be sequence-detected in the sequence detecting module 800, the received waveform is cut according to the waveform transmission time interval, and the cut waveform is decoded according to a certain decoding algorithm. Figure 8 shows a block diagram of the receive end sequence detection module of the OvTDM system. As shown, the sequence detection module 800 can include an analysis storage unit 810, a comparison unit 820, and a retention path storage unit and an Euclidean distance storage unit 830. During the detection process, the analysis storage unit makes a complex convolutional coding model and a trellis diagram of the OvTDM system, and lists all states of the OvTDM system and stores them. The comparison unit searches for a path with a minimum Euclidean distance of the received digital signal according to the trellis diagram in the analysis storage unit, and the reserved path storage unit and the Euclidean distance storage unit are respectively used to store the reserved path and the Euclidean output of the comparison unit. Distance or weighted Euclidean distance. The reserved path storage unit and the Euclidean distance storage unit need to be prepared for each stable state. The reserved path storage unit length may preferably be 4K to 5K. The Euclidean distance storage unit preferably stores only relative distances.
以上作为示例介绍了OvTDM系统的发送和接收端的处理过程。尽管OvXDM系统具有相应的接收解调方案来排除信号在时域或频域的重叠所带来的干扰,但是频谱利用率的大幅提高仍然对信号的接收提出了更高要求。 The above describes the processing of the transmitting and receiving ends of the OvTDM system as an example. Although the OvXDM system has a corresponding receive demodulation scheme to eliminate the interference caused by the overlap of signals in the time domain or the frequency domain, the substantial increase in spectrum utilization still imposes higher requirements on signal reception.
一般的通信系统中都需要设计训练序列,其作用主要是在收到信号后经过处理,可同时实现定时同步、载波同步和信道估计。定时同步、载波同步和信道估计是接收端正确接收的三个最重要环节。因此,训练符号的设计至关重要,特别是对于OvXDM系统这种超高频谱效率的通信系统尤其如此。如果这三个步骤中任一步骤误差较大,对整个系统的影响将会很大,后续的译码过程也就没有意义了。In the general communication system, it is necessary to design a training sequence, which mainly functions after receiving the signal, and can simultaneously implement timing synchronization, carrier synchronization and channel estimation. Timing synchronization, carrier synchronization and channel estimation are the three most important steps for the receiver to receive correctly. Therefore, the design of training symbols is critical, especially for the ultra-high spectral efficiency communication systems of the OvXDM system. If the error of any of these three steps is large, the impact on the whole system will be great, and the subsequent decoding process will be meaningless.
目前通信系统常采用M序列为训练序列,由于M序列自相关和互相关特性较差,导致系统同步过程成功率低,网络接入慢。图9示出了M序列的自相关特性,从图中可以看到其自相关特性间隔一定时间都会出现脉冲,其自相关特性不是很好。因此在信号处理过程中,对时间和频率的同步精度较差,降低用户接入网络的成功率和接入速度,使用户体验变差。At present, the M-series is often used as the training sequence in the communication system. Due to the poor autocorrelation and cross-correlation properties of the M-sequence, the success rate of the system synchronization process is low and the network access is slow. Fig. 9 shows the autocorrelation property of the M-sequence. It can be seen from the figure that the autocorrelation property has a pulse at a certain time interval, and its autocorrelation property is not very good. Therefore, in the signal processing process, the synchronization accuracy of time and frequency is poor, and the success rate and access speed of the user accessing the network are reduced, and the user experience is deteriorated.
根据本发明的一方面,在OvXDM系统中利用完备正交互补码对偶设计训练序列。经研究发现,完备正交互补码具有自相关函数在原点是理想的冲激函数,原点以外处处为零,而互相关函数处处为零的特性。这对于训练序列而言是及其有利的属性。In accordance with an aspect of the invention, a training sequence is designed using a complete orthogonal complementary code dual in an OvXDM system. It is found that the complete orthogonal complementary code has an autocorrelation function which is an ideal impulse function at the origin, zero everywhere except the origin, and the cross-correlation function is zero. This is an advantageous attribute for the training sequence.
以下简要介绍完备正交互补码的生成方法。The following is a brief introduction to the method of generating a complete orthogonal complementary code.
完备正交互补码具有对偶关系,生成方法是根据最短基本互补码求解出与之完全正交互补的另一对最短基本互补码。由于互补特性,其特点为自相关函数在原点是理想的冲击函数,原点以外处处为零,而互相关函数处处为零。因此可使用在通信系统中作为训练序列使用。The complete orthogonal complementary code has a dual relationship, and the generating method is to solve another pair of shortest basic complementary codes which are completely orthogonally complementary according to the shortest basic complementary code. Due to the complementary nature, the autocorrelation function is an ideal impact function at the origin, zero everywhere except the origin, and the cross-correlation function is everywhere zero. It can therefore be used as a training sequence in a communication system.
基本完备正交互补码对偶的生成步骤如下:The steps for generating the basic complete orthogonal complementary code dual are as follows:
(1)根据编码约束长度选定基本完备正交互补码对偶的长度N0(1) The length N 0 of the pair of substantially complete orthogonal complementary codes is selected according to the length of the coding constraint.
(2)按照关系N0=L0*2l(l=0,1,2...)(2) According to the relationship N 0 = L 0 * 2 l (l = 0, 1, 2...)
先决定一个最短基本完备互补码对的长度L0。基本完备互补码中只有一对分量码,它只要求其非周期自相关特性的互补性。First determine the length L 0 of a shortest basic complete complementary code pair. There is only one pair of component codes in the basic complete complementary code, which only requires the complementarity of its aperiodic autocorrelation properties.
或者按照关系N0=L01*L02*2l+1(l=0,1,2...),先决定两个最短基本完备互补码的长度L01,L02Or according to the relationship N 0 =L 01 *L 02 *2 l+1 (l=0,1,2...), the lengths L 01 , L 02 of the two shortest basic complete complementary codes are determined first.
(3)根据(2)选定的最短码长及工程实现需求,任意选定一码长为最短码长L0
Figure PCTCN2017105601-appb-000001
码,
Figure PCTCN2017105601-appb-000002
(3) arbitrarily select a code length to the shortest code length L 0 according to (2) the selected shortest code length and engineering implementation requirements.
Figure PCTCN2017105601-appb-000001
code,
Figure PCTCN2017105601-appb-000002
(4)根据非周期自相关函数完全互补性的要求,求解出与
Figure PCTCN2017105601-appb-000003
非周期自相关函数完全互补的
Figure PCTCN2017105601-appb-000004
码,
Figure PCTCN2017105601-appb-000005
(4) According to the requirements of the complete complementarity of the aperiodic autocorrelation function,
Figure PCTCN2017105601-appb-000003
The aperiodic autocorrelation function is completely complementary
Figure PCTCN2017105601-appb-000004
code,
Figure PCTCN2017105601-appb-000005
(5)根据(4)解出的最短基本互补码对
Figure PCTCN2017105601-appb-000006
解出与之完全互补正交的另一对 最短基本互补码对
Figure PCTCN2017105601-appb-000007
新得到的一对最短基本互补码
Figure PCTCN2017105601-appb-000008
也具有完备的非周期自相关特性。这两对码就构成了完备正交互补码对偶,从互补意义上讲,它们中每一对的非周期自相关函数以及两对之间的非周期互相关函数都是理想的。
(5) The shortest basic complementary code pair solved according to (4)
Figure PCTCN2017105601-appb-000006
Solving another pair of shortest basic complementary code pairs that are completely complementary to it
Figure PCTCN2017105601-appb-000007
Newly obtained pair of shortest basic complementary codes
Figure PCTCN2017105601-appb-000008
It also has complete aperiodic autocorrelation properties. The two pairs of codes constitute a complete orthogonal complementary code dual. In the complementary sense, the aperiodic autocorrelation function of each pair and the aperiodic cross-correlation function between the two pairs are ideal.
(6)从码长为L0的完备正交互补码对偶形成所需长度N0=L0*2l(l=0,1,2...)的完备正交互补码对偶。(6) A complete orthogonal complementary code pair of the required length N 0 = L 0 * 2 l (l = 0, 1, 2...) is formed from the complete orthogonal complementary code pair having a code length of L 0 .
有如下几种方法可以将码长加倍,而长度加倍后的两个新码对,仍然是完备正交码对偶。其中
Figure PCTCN2017105601-appb-000009
表示非序列,即元素值全部取反值。
There are several ways to double the code length, and the two new code pairs after the length is doubled are still complete orthogonal code pairs. among them
Figure PCTCN2017105601-appb-000009
Represents a non-sequence, that is, all element values are inverted.
方法一:将短码按照如下方法串接起来Method 1: Connect the short codes as follows:
Figure PCTCN2017105601-appb-000010
Figure PCTCN2017105601-appb-000010
Figure PCTCN2017105601-appb-000011
Figure PCTCN2017105601-appb-000011
方法二:C0(S0)码的奇偶位分别由
Figure PCTCN2017105601-appb-000012
Figure PCTCN2017105601-appb-000013
组成;C1(S1)码的奇偶位分别由
Figure PCTCN2017105601-appb-000014
Figure PCTCN2017105601-appb-000015
组成。
Method 2: The parity of the C 0 (S 0 ) code is respectively
Figure PCTCN2017105601-appb-000012
and
Figure PCTCN2017105601-appb-000013
Composition; the parity of the C 1 (S 1 ) code is respectively
Figure PCTCN2017105601-appb-000014
and
Figure PCTCN2017105601-appb-000015
composition.
方法三:将短码按下述方法串接起来:Method 3: Connect the short codes in the following way:
Figure PCTCN2017105601-appb-000016
Figure PCTCN2017105601-appb-000016
Figure PCTCN2017105601-appb-000017
Figure PCTCN2017105601-appb-000017
方法四:C0码的奇偶位分别由
Figure PCTCN2017105601-appb-000018
Figure PCTCN2017105601-appb-000019
组成;S0码的奇偶位分别由
Figure PCTCN2017105601-appb-000020
Figure PCTCN2017105601-appb-000021
组成;C1码的奇偶位分别由
Figure PCTCN2017105601-appb-000022
Figure PCTCN2017105601-appb-000023
组成;S1码的奇偶位分别由
Figure PCTCN2017105601-appb-000024
Figure PCTCN2017105601-appb-000025
组成。
Method 4: The parity bits of the C 0 code are respectively
Figure PCTCN2017105601-appb-000018
and
Figure PCTCN2017105601-appb-000019
Composition; the parity of the S 0 code is respectively
Figure PCTCN2017105601-appb-000020
and
Figure PCTCN2017105601-appb-000021
Composition; the parity of the C 1 code is determined by
Figure PCTCN2017105601-appb-000022
and
Figure PCTCN2017105601-appb-000023
Composition; the parity of the S 1 code is respectively
Figure PCTCN2017105601-appb-000024
and
Figure PCTCN2017105601-appb-000025
composition.
连续使用上述方法,最终形成长度为N0的完备正交互补对偶码。Using the above method continuously, a complete orthogonal complementary dual code of length N 0 is finally formed.
图10示出了完备正交互补码对偶的自相关特性。Figure 10 shows the autocorrelation properties of a complete orthogonal complementary code pair.
训练序列设计Training sequence design
由于完备互补正交码对偶具有自相关函数在原点是理想的冲击函数,原点以外处处为零,而互相关函数处处为零的特性。因此本专利中采用完备互补正交码对偶设计OvXDM系统的训练序列,其格式为[Tsc]N,TSC(Training Sequence Code,训练序列),N表示训练序列长度,完备互补正交码对偶的生成方法如上所述。例如可以选取训练序列的长度N=20。Since the complete complementary orthogonal code dual has an autocorrelation function which is an ideal impact function at the origin, the origin is zero except for the origin, and the cross-correlation function is zero. Therefore, in this patent, the training sequence of the OvXDM system is designed by using the complete complementary orthogonal code duality. The format is [Tsc] N , TSC (Training Sequence Code), N is the length of the training sequence, and the generation of the complete complementary orthogonal code dual is generated. The method is as described above. For example, the length of the training sequence can be selected as N=20.
即使用一个完备互补正交码对偶即可完成同步中的定时同步、载波同步和信道估计三个过程。That is, the process of timing synchronization, carrier synchronization and channel estimation in synchronization can be completed by using a complete complementary orthogonal code dual.
需要说明的是,LAS码也是由完备互补正交码生成,其格式为[Cn 0 Sn]N包括C 码、S码和零码。本案例中设计的训练序列格式为[Cn Sn]N仅包括C码和S码,没有零码。It should be noted that the LAS code is also generated by a complete complementary orthogonal code, and its format is [C n 0 S n ] N including C code, S code and zero code. The training sequence format designed in this case is [C n S n ] N includes only the C code and the S code, and there is no zero code.
定时同步过程Timing synchronization process
接收机收到信号,需要先跟通信系统保持同步,包括定时同步和载波同步。定时同步的原理是通过匹配滤波方法,直接将接收信号与本地完备互补正交码码求自相关运算,得到自相关峰值。从相关峰值中根据一定的方法找到训练符号的位置。找到训练符号的位置也就确定了当前帧的起始位置,即完成了接收信号和系统的时间同步,定时同步过程结束。The receiver receives the signal and needs to synchronize with the communication system first, including timing synchronization and carrier synchronization. The principle of timing synchronization is to directly correlate the received signal with the local complete complementary orthogonal code code through the matched filtering method to obtain the autocorrelation peak. The position of the training symbol is found from the correlation peak according to a certain method. The position of the training symbol is also determined to determine the starting position of the current frame, that is, the time synchronization of the received signal and the system is completed, and the timing synchronization process ends.
如前所述,由于完备互补正交码的自相关和互相关特性都比较好,将完备互补正交码用于设计训练符号。由此,在计算接收信号和完备互补正交码的相关运算时,峰值大小分布差异较大,通过合理的设置阈值,可以很精确的找到完备互补正交码的起始位置,定时精度较高。As mentioned above, since the autocorrelation and cross-correlation properties of the complete complementary orthogonal codes are better, the complete complementary orthogonal codes are used to design the training symbols. Therefore, when calculating the correlation operation between the received signal and the complete complementary orthogonal code, the peak size distribution is quite different. By setting the threshold reasonably, the starting position of the complete complementary orthogonal code can be accurately found, and the timing precision is high. .
具体在寻找完备互补正交码的相关峰值时,根据训练符号结构,采取合适的信号接收长度,使用滑窗法自相关运算方式,将接收信号与本地完备互补正交码求相关运算寻找自相关峰值来确定完备互补正交码的位置。例如,这里的信号接收长度可保证至少涵盖有完备互补正交码,以确保能检测到峰值。Specifically, when looking for the correlation peak of the complete complementary orthogonal code, according to the training symbol structure, adopt appropriate signal receiving length, and use the sliding window method autocorrelation operation method to find the autocorrelation between the received signal and the local complete complementary orthogonal code. The peak value is used to determine the position of the complete complementary orthogonal code. For example, the signal reception length here is guaranteed to cover at least a complete complementary orthogonal code to ensure that a peak can be detected.
所谓的滑窗法自相关运算,是以完备互补正交码的长度为窗口长度对接收信号作取窗处理,将当前窗口内的这段信号与本地的完备互补正交码作相关运算,从而得到一个自相关结果。然后,将窗口向后滑动,再对接收信号进行取窗,将当前窗口内的这段信号与本地的完备互补正交码再作相关运算,从而再得到一个相关结果。以此方式,不断滑动窗口,直至对接收到的信号全部进行了相关运算。从计算得出的全部自相关结果,通过设置阈值,即超过阈值的自相关结果作为峰值,找到完备互补正交码的位置。The so-called sliding window method autocorrelation operation is to take a window processing on the received signal with the length of the complete complementary orthogonal code as the window length, and correlate the signal in the current window with the local complete complementary orthogonal code, thereby Get an autocorrelation result. Then, the window is slid backward, and then the received signal is windowed, and the signal in the current window is correlated with the local complete complementary orthogonal code, thereby obtaining a correlation result. In this way, the window is continuously slid until all the received signals are correlated. From the calculated autocorrelation results, the position of the complete complementary orthogonal code is found by setting the threshold, that is, the autocorrelation result exceeding the threshold as the peak value.
载波同步过程Carrier synchronization process
接收到信号后,需要先跟通信系统保持同步,包括定时同步和载波同步,接收信号和系统先保持时间上的同步,通过定时同步获取完备互补正交码的起始位置,再进行频率的同步。After receiving the signal, it needs to synchronize with the communication system first, including timing synchronization and carrier synchronization. The received signal and the system first maintain time synchronization, obtain the starting position of the complete complementary orthogonal code through timing synchronization, and then synchronize the frequency. .
以完备互补正交码对偶生成训练序列xn,信号采样间隔为T,以载频f0执行调制,则发射端发射出去的信号为
Figure PCTCN2017105601-appb-000026
即将信号调制到f0载频上。经过无线 信道传输后信号引入时偏τ和频偏Δf,接收端收到信号后先进行定时同步,以去除时间偏移τ,再对信号进行载波同步,以去除频偏并校正,载波同步过程如下:
The training sequence x n is generated by the complete complementary orthogonal code dual, the signal sampling interval is T, and the modulation is performed at the carrier frequency f 0 , then the signal transmitted by the transmitting end is
Figure PCTCN2017105601-appb-000026
That is, the signal is modulated onto the f 0 carrier frequency. After the wireless channel is transmitted, the signal is induced with a bias τ and a frequency offset Δf. After receiving the signal, the receiving end performs timing synchronization to remove the time offset τ, and then performs carrier synchronization on the signal to remove the frequency offset and correct the carrier synchronization process. as follows:
(1)解调(1) Demodulation
对接收信号解调,根据以下公式将信号搬移到基带:Demodulate the received signal and move the signal to baseband according to the following formula:
Figure PCTCN2017105601-appb-000027
Figure PCTCN2017105601-appb-000027
其中f0′是接收端的载频,包含了频偏,可表示为f0′=f0-Δf。Where f 0 ' is the carrier frequency of the receiving end, including the frequency offset, which can be expressed as f 0 '=f 0 -Δf.
(2)计算接收信号yn和本地训练序列xn的互相关性,需要说明的是,在此步骤中的接收信号yn已进行了定时同步,因此在互相关的计算中,实际上是在对接收信号的训练序列和本地训练序列进行求互相关性的操作:(2) calculating the reception signal y n x n a training sequence and a local cross-correlation it should be noted that the received signal y n in this step has been carried out timing synchronization, so the cross-correlation calculation is actually Performing cross-correlation operations on the training sequence of the received signal and the local training sequence:
Figure PCTCN2017105601-appb-000028
Figure PCTCN2017105601-appb-000028
其中,a表示
Figure PCTCN2017105601-appb-000029
的模值,*表示共轭。
Where a represents
Figure PCTCN2017105601-appb-000029
The modulus value, * indicates conjugate.
(3)计算信号之间的互相关性R(3) Calculate the cross-correlation between signals R
Figure PCTCN2017105601-appb-000030
其中N为训练序列的长度,该公式中的n为对应的索引。
Figure PCTCN2017105601-appb-000030
Where N is the length of the training sequence, and n in the formula is the corresponding index.
(4)计算频偏Δf(4) Calculate the frequency offset Δf
Figure PCTCN2017105601-appb-000031
其中angle为求角度函数。
Figure PCTCN2017105601-appb-000031
Where angle is the angle function.
(5)对接收信号进行频偏校正:(5) Perform frequency offset correction on the received signal:
根据计算出的频偏Δf,对接收信号进行频偏校正,即恢复出原始发送训练序列。According to the calculated frequency offset Δf, the received signal is subjected to frequency offset correction, that is, the original transmission training sequence is restored.
yn′=yne-j2πΔfnT=xnej2πΔfnTe-j2πΔfnT=xn y n '=y n e -j2πΔfnT =x n e j2πΔfnT e -j2πΔfnT =x n
大多数通信系统需要进行粗频偏和细频偏两次校正才能较准确的得出系统频偏,计算过程繁琐复杂,根据本发明的同步方案,采用完备正交互补码对偶为训练序列时,只用一个互补码就可以精确的计算出系统频偏,并省去了繁琐的计算过程,为后续的信道估计过程和译码过程奠定了基础,降低整个系统的误码率。Most communication systems need to perform coarse frequency offset and fine frequency offset twice correction to obtain the system frequency offset more accurately. The calculation process is cumbersome and complicated. According to the synchronization scheme of the present invention, when the complete orthogonal complementary code dual is used as the training sequence, The system frequency offset can be accurately calculated by using only one complementary code, and the cumbersome calculation process is omitted, which lays a foundation for the subsequent channel estimation process and decoding process, and reduces the bit error rate of the whole system.
图11示出了根据本发明的一实施例的载波同步装置1100的框图。出于完整起见,载波同步装置1100可包括解调单元1110。解调单元1110可用于将接收信号首先解调至基带,以用于后续操作。FIG. 11 shows a block diagram of a carrier synchronization device 1100 in accordance with an embodiment of the present invention. For the sake of completeness, the carrier synchronization device 1100 may include a demodulation unit 1110. Demodulation unit 1110 can be used to first demodulate the received signal to baseband for subsequent operation.
载波同步装置1100还可包括互相关计算单元1120和频率校正单元1130,它们可以是上文结合图7所讨论的同步单元的一部分。The carrier synchronization device 1100 may also include a cross correlation calculation unit 1120 and a frequency correction unit 1130, which may be part of the synchronization unit discussed above in connection with FIG.
互相关计算单元1120可执行互相关运算。在本发明中,互相关计算单元1120可首先将接收信号中的训练序列与本地的训练序列执行互相关运算,以获得互相关结 果,然后将该互相关结果与其自身的延迟版本执行互相关运算以获得接收端与发射端之间的频偏。The cross correlation calculation unit 1120 can perform a cross correlation operation. In the present invention, the cross-correlation calculation unit 1120 may first perform a cross-correlation operation on the training sequence in the received signal and the local training sequence to obtain a cross-correlation knot. Then, the cross-correlation result is subjected to a cross-correlation operation with its own delayed version to obtain a frequency offset between the receiving end and the transmitting end.
频率校正单元1130可基于获得的频偏来校正接收信号以消除接收信号中的频偏。The frequency correcting unit 1130 may correct the received signal based on the obtained frequency offset to cancel the frequency offset in the received signal.
较优地,训练序列可包括完备互补正交对偶码,例如LAS码。当然,在其他实施例中,训练序列也可以使用伪随机码,例如m序列、或Gold序列,或者使用Golomb码、或CAN码。Preferably, the training sequence may comprise a complete complementary orthogonal dual code, such as a LAS code. Of course, in other embodiments, the training sequence may also use a pseudo-random code, such as an m-sequence, or a Gold sequence, or a Golomb code, or a CAN code.
图12示出了根据一实施例的载波同步方法的流程图。如图所示,载波同步方法可包括以下步骤:Figure 12 shows a flow chart of a carrier synchronization method in accordance with an embodiment. As shown, the carrier synchronization method can include the following steps:
步骤1201:将接收信号中的训练序列与本地的训练序列执行互相关运算,以获得互相关结果;Step 1201: Perform a cross-correlation operation on the training sequence in the received signal and the local training sequence to obtain a cross-correlation result.
步骤1202:将该互相关结果与该互相关结果的延迟版本执行互相关运算以获得接收端与发射端之间的频偏;以及Step 1202: Perform a cross-correlation operation on the cross-correlation result and the delayed version of the cross-correlation result to obtain a frequency offset between the receiving end and the transmitting end;
步骤1203:基于该频偏对接收信号执行频偏校正。Step 1203: Perform frequency offset correction on the received signal based on the frequency offset.
尽管为使解释简单化将上述方法图示并描述为一系列动作,但是应理解并领会,这些方法不受动作的次序所限,因为根据一个或多个实施例,一些动作可按不同次序发生和/或与来自本文中图示和描述或本文中未图示和描述但本领域技术人员可以理解的其他动作并发地发生。Although the above method is illustrated and described as a series of acts for simplicity of the explanation, it should be understood and appreciated that these methods are not limited by the order of the acts, as some acts may occur in different orders in accordance with one or more embodiments. And/or concurrently with other acts from what is illustrated and described herein or that are not illustrated and described herein, but are understood by those skilled in the art.
信道估计过程Channel estimation process
信号经过信道传输,由于信道环境较为复杂,接收的信号存在时偏和频偏,也可能是由多条路径经过反射到达接收端,接收端在收到信号后,先通过定时同步、载波同步去时偏和频偏,保持和发送端同步,由于多径,还需要进行信道估计,以估计出信道参数,之后再进行译码。The signal is transmitted through the channel. Due to the complicated channel environment, the received signal has time offset and frequency offset. It may also be reflected by multiple paths to the receiving end. After receiving the signal, the receiving end first passes the timing synchronization and carrier synchronization. The time offset and the frequency offset are kept in sync with the transmitting end. Due to the multipath, channel estimation is also needed to estimate the channel parameters, and then decoding is performed.
将信道表示为h={h0,h1,…,hL-1},其中L为信道多径数目。The channel is represented as h = {h 0 , h 1 , ..., h L-1 }, where L is the number of channel multipaths.
训练序列可以表示为x={x0,x1,...,N-1},其中N为训练序列长度,例如可以取20。The training sequence can be expressed as x = {x 0 , x 1 , ..., N-1 }, where N is the length of the training sequence, for example 20 can be taken.
在接收端收到的信息y={y0,y1,...yN-1}可表示为
Figure PCTCN2017105601-appb-000032
其中
Figure PCTCN2017105601-appb-000033
为卷积操作,即yn=xnh0+xn-1h1+…xn-L+1hL-1,L-1≤n≤N-1。上式可以表示为矩阵形式Y=X×H,,其中Y是接收数据矩阵Y=[yi,yi+1,…,yi+M-1]T,大小为M×1,H是多径信道矩阵H=[h0,h1,…,hL-1]T,大小为L×1,X是发送训练序列矩阵
Figure PCTCN2017105601-appb-000034
大小为M×L,其中M的取值为L≤M≤N-L,其含义为采用部分接收符号信息和部分发送训练序列,根据最小二乘的方法可求出多径信道模型H。其中M的取值越大结果越精确,例如在本案中可以取M=N-L。
The information y={y 0 , y 1 ,...y N-1 } received at the receiving end can be expressed as
Figure PCTCN2017105601-appb-000032
among them
Figure PCTCN2017105601-appb-000033
It is a convolution operation, that is, y n = x n h 0 + x n-1 h 1 + ... x n - L + 1 h L-1 , L- 1n ≤ N-1. The above equation can be expressed as a matrix form Y=X×H, where Y is the received data matrix Y=[y i , y i+1 ,..., y i+M-1 ] T , the size is M×1, H is Multipath channel matrix H = [h 0 , h 1 , ..., h L-1 ] T , size L × 1, X is the transmission training sequence matrix
Figure PCTCN2017105601-appb-000034
The size is M×L, where the value of M is L≤M≤NL, which means that the partial received symbol information and the partial transmission training sequence are used, and the multipath channel model H can be obtained according to the least squares method. The larger the value of M is, the more accurate the result is. For example, in the present case, M=NL can be taken.
将矩阵形式展开可表示为:Expanding the matrix form can be expressed as:
Figure PCTCN2017105601-appb-000035
i的取值为L-1≤i≤N-L
Figure PCTCN2017105601-appb-000035
The value of i is L-1≤i≤NL
信道估计的目的是由公式Y=X×H估计出信道向量H,其中X是发送的训练序列,Y是接收到的训练序列,它们是已知的。The purpose of the channel estimation is to estimate the channel vector H from the formula Y = X x H, where X is the transmitted training sequence and Y is the received training sequence, which are known.
在本发明中,对于这种信道,采用最小二乘法作为信道估计方法,如下式所示
Figure PCTCN2017105601-appb-000036
其中
Figure PCTCN2017105601-appb-000037
为信道估计值,(·)H为求矩阵共轭转置操作,(·)-1为矩阵求逆操作。
In the present invention, for such a channel, a least squares method is employed as the channel estimation method as shown in the following equation.
Figure PCTCN2017105601-appb-000036
among them
Figure PCTCN2017105601-appb-000037
For the channel estimation value, (·) H is the matrix conjugate transpose operation, and (·) -1 is the matrix inversion operation.
通过数学矩阵模型快速的求解出信道参数h,后续进行信道均衡,以去除掉信道特性对信号的影响,恢复出原始信号。The channel parameter h is quickly solved by the mathematical matrix model, and the channel equalization is performed subsequently to remove the influence of the channel characteristics on the signal and recover the original signal.
需要说明的是,由于训练序列是已知的,可将(XHX)-1XH的结果提前计算好,存储在本地,在实际通信过程,避免了每次都要计算。It should be noted that since the training sequence is known, the result of (X H X) -1 X H can be calculated in advance and stored locally, and in the actual communication process, the calculation is avoided every time.
大多通信系统的信道估计都是计算复杂的卷积过程,运算过程较为复杂。根据本发明的信道估计方案,利用最小二乘法,将复杂的卷积模型简化为矩阵运算,在简化运算过程的同时保证信道估计值的精确性,降低信道估计模型与理想信道模型的偏差,提高系统后续译码过程的成功率,降低系统误码率。The channel estimation of most communication systems is a complex convolution process, and the operation process is complicated. According to the channel estimation scheme of the present invention, the complex convolution model is simplified into a matrix operation by using the least squares method, the accuracy of the channel estimation value is ensured while simplifying the operation process, and the deviation between the channel estimation model and the ideal channel model is improved, and the deviation is improved. The success rate of the subsequent decoding process of the system reduces the system error rate.
图13示出了根据本发明的一实施例的信道估计装置1300的框图。出于完整起见,信道估计装置1300可包括同步单元1310。同步单元1310可用于检测接收信号中的训练序列,其可以是上文参照图7讨论的同步单元710的一部分。信道估计装置1300还可包括矩阵运算单元1320,对基于本地训练序列的第一矩阵与基于接收信号中训练序列的第二矩阵执行矩阵运算以获得信道估计值,这在上文进行了详细描述,在此不再赘述。即,矩阵运算单元1320是一变换单元,通过对信号矩阵的矩阵变换就可实现信道估计功能,具体而言,这里通过最小二乘法执行该矩阵运算。FIG. 13 shows a block diagram of a channel estimation apparatus 1300 in accordance with an embodiment of the present invention. For the sake of completeness, the channel estimation device 1300 can include a synchronization unit 1310. Synchronization unit 1310 can be used to detect a training sequence in the received signal, which can be part of synchronization unit 710 discussed above with respect to FIG. The channel estimation apparatus 1300 may further include a matrix operation unit 1320 that performs a matrix operation on the first matrix based on the local training sequence and the second matrix based on the training sequence in the received signal to obtain a channel estimation value, which is described in detail above. I will not repeat them here. That is, the matrix operation unit 1320 is a transform unit, and the channel estimation function can be realized by matrix transformation of the signal matrix. Specifically, the matrix operation is performed by the least squares method here.
如上所述,这里基于本地训练序列的第一矩阵的列数等于信道的多径数目,所获 得的信道估计值为多径信道估计值。As described above, the number of columns of the first matrix based on the local training sequence is equal to the number of multipaths of the channel. The resulting channel estimate is a multipath channel estimate.
较优地,训练序列可包括完备互补正交对偶码,例如LAS码。当然,在其他实施例中,训练序列也可以使用伪随机码,例如m序列、或Gold序列,或者使用Golomb码、或CAN码。Preferably, the training sequence may comprise a complete complementary orthogonal dual code, such as a LAS code. Of course, in other embodiments, the training sequence may also use a pseudo-random code, such as an m-sequence, or a Gold sequence, or a Golomb code, or a CAN code.
图14示出了根据一实施例的信道估计方法的流程图。如图所示,信道估计方法可包括以下步骤:Figure 14 shows a flow chart of a channel estimation method in accordance with an embodiment. As shown, the channel estimation method can include the following steps:
步骤1401:检测接收信号中的训练序列。Step 1401: Detect a training sequence in the received signal.
具体地,检测接收信号中的训练序列是通过使用滑窗法将接收信号与本地的训练序列执行自相关运算并检测自相关峰值来进行的。Specifically, detecting the training sequence in the received signal is performed by performing an autocorrelation operation on the received signal with the local training sequence and detecting the autocorrelation peak using a sliding window method.
步骤1402:对基于本地训练序列的第一矩阵与基于接收信号中训练序列的第二矩阵执行矩阵运算以获得信道估计值。Step 1402: Perform a matrix operation on the first matrix based on the local training sequence and the second matrix based on the training sequence in the received signal to obtain a channel estimation value.
在一实例中,利用最小二乘法对第一矩阵和第二矩阵执行该矩阵运算。这里基于本地训练序列的第一矩阵的列数等于信道的多径数目,所获得的信道估计值为多径信道估计值。In an example, the matrix operation is performed on the first matrix and the second matrix using a least squares method. Here, the number of columns of the first matrix based on the local training sequence is equal to the number of multipaths of the channel, and the obtained channel estimation value is a multipath channel estimation value.
较优地,训练序列可包括完备互补正交对偶码,例如LAS码。当然,在其他实施例中,训练序列也可以使用伪随机码,例如m序列、或Gold序列,或者使用Golomb码、或CAN码。Preferably, the training sequence may comprise a complete complementary orthogonal dual code, such as a LAS code. Of course, in other embodiments, the training sequence may also use a pseudo-random code, such as an m-sequence, or a Gold sequence, or a Golomb code, or a CAN code.
设计训练序列频宽Design training sequence bandwidth
本系统中设计符号结构包括训练序列TSC(traning sequence code)和数据(data)。训练符号的设计至关重要,影响了整个系统的定时、同步、信道估计三个最重要的环节,如果这三个步骤中任一步骤误差较大,对整个系统的影响将会很大,后续的译码过程也就没有意义了。The design symbol structure in the system includes a training sequence TSC (traning sequence code) and data (data). The design of training symbols is very important, which affects the three most important aspects of timing, synchronization and channel estimation of the whole system. If any of these three steps has large errors, the impact on the whole system will be great. The decoding process is meaningless.
训练序列频宽的设计过程较为复杂,频宽较短时其对应的功率谱密度较大,当系统中存在多个载波时会影响数据的接收和发送,频宽过大时对应的功率谱密度太小,对系统的发送机和接收机的灵敏度要求极高。The design process of the training sequence bandwidth is more complicated. When the bandwidth is short, the corresponding power spectral density is large. When there are multiple carriers in the system, the data reception and transmission will be affected. When the bandwidth is too large, the corresponding power spectral density will be affected. Too small, the sensitivity of the transmitter and receiver of the system is extremely high.
在现有通信系统中,一般采用训练序列和数据的频宽相同的方法,其对应的功率谱密度相同,如图15所示,且由于一般系统中频宽都较短,因此对应于时域发送时间较长,影响信号同步、信道估计处理时间过程,后续译码过程等待时间也变长,降低了系统的传输速率。另外,由于训练序列发送时间较长,因此在对信号进行采样时,其采样率较低,时间分辨率不够精细,影响信道估计的偏差。 In the existing communication system, the method in which the training sequence and the data have the same bandwidth is generally adopted, and the corresponding power spectral density is the same, as shown in FIG. 15, and since the bandwidth is short in the general system, it corresponds to the time domain transmission. The longer time affects the signal synchronization and channel estimation processing time, and the waiting time of the subsequent decoding process also becomes longer, which reduces the transmission rate of the system. In addition, since the training sequence has a long transmission time, when the signal is sampled, the sampling rate is low, and the temporal resolution is not fine enough, which affects the deviation of the channel estimation.
本发明通过扩频码将训练序列扩展到较宽频带上,使得训练序列频宽远大于数据频宽(例如,5倍、10倍或以上),其训练序列、数据的频宽和功率谱密度关系图如附图16所示。由于训练序列和数据的发送功率需保持一致,由图中可以看出,当训练序列的频宽变宽后,其对应的功率谱密度随之也会大幅度降低,相对于数据功率谱密度而言是很低的。The invention extends the training sequence to a wider frequency band by using a spreading code such that the training sequence bandwidth is much larger than the data bandwidth (for example, 5 times, 10 times or more), the training sequence, the data bandwidth and the power spectral density. The relationship diagram is shown in Figure 16. Since the transmission power of the training sequence and the data need to be consistent, it can be seen from the figure that when the bandwidth of the training sequence is widened, the corresponding power spectral density is also greatly reduced, relative to the data power spectral density. The words are very low.
本系统可以使用所有的可用扩频码,包括完备互补正交对偶码(例如,LAS码)、伪随机码(m序列、Gold序列)、Golomb码、CAN(Cyclic Algorithm New)等。本系统中我们以完备互补正交码为例,介绍定时同步、载波同步和信道估计的处理过程。完备互补正交对偶码的特点是自相关函数在原点是理想的冲击函数,原点以外处处为零,而互相关函数处处为零,完备互补正交对偶码的自相关特性如附图10所示。因此当训练序列重叠时也不会相互造成干扰。这样设计可以提高系统的频谱利用率和传输速率。The system can use all available spreading codes, including complete complementary orthogonal dual codes (eg, LAS codes), pseudo random codes (m sequences, Gold sequences), Golomb codes, CAN (Cyclic Algorithm New), and the like. In this system, we take the complete complementary orthogonal code as an example to introduce the processing of timing synchronization, carrier synchronization and channel estimation. The characteristic of the complete complementary orthogonal dual code is that the autocorrelation function is an ideal impact function at the origin, zero everywhere except the origin, and the cross-correlation function is everywhere zero. The autocorrelation property of the complete complementary orthogonal dual code is shown in Fig. 10. . Therefore, when the training sequences overlap, they do not cause interference with each other. This design can improve the spectrum utilization and transmission rate of the system.
由公式
Figure PCTCN2017105601-appb-000038
可知,当频域频宽越大时,其对应在时域的时间越小,即在较短的时间内就可以完成训练序列的发送和接收过程。在信号接收过程,对于同样长度的数据,当接收时间变短,可以将信号的采样率提高,使得时间分辨率更精细。在信道估计过程提高时间分辨率的精确度,使得信道估计结果更精确。
By formula
Figure PCTCN2017105601-appb-000038
It can be seen that when the frequency domain bandwidth is larger, the time corresponding to the time domain is smaller, that is, the transmission and reception process of the training sequence can be completed in a shorter time. In the signal receiving process, for the same length of data, when the receiving time becomes shorter, the sampling rate of the signal can be increased, so that the time resolution is finer. The accuracy of the temporal resolution is improved during the channel estimation process, making the channel estimation result more accurate.
在一方面,由于训练序列的功率谱密度极低,几乎不会对数据信号产生影响,因此训练序列和数据可在同一时间叠加发送。当有两个载波信号同时发送数据时,其构造图如附图17所示,从图中可以看出,两个载波所承载的实际数据中间有保护带,不会重叠也不会相互造成干扰;而训练序列的频宽和实际数据有重叠,由于训练序列功率谱密度非常低,因此不会对实际数据造成干扰;再有,不同的训练序列可用不同的扩频码加以区分,不会造成混淆。训练序列不独占特定的频率和时间资源,提高了系统的频谱利用率和传输速率。In one aspect, since the power spectral density of the training sequence is extremely low, there is little impact on the data signal, so the training sequence and data can be superimposed and transmitted at the same time. When there are two carrier signals transmitting data at the same time, the structure diagram is as shown in Fig. 17. It can be seen from the figure that the actual data carried by the two carriers has guard bands in the middle, which will not overlap or interfere with each other. The bandwidth of the training sequence overlaps with the actual data. Since the power spectrum density of the training sequence is very low, it does not cause interference to the actual data. Furthermore, different training sequences can be distinguished by different spreading codes, which will not cause Confused. The training sequence does not monopolize specific frequency and time resources, improving the spectrum utilization and transmission rate of the system.
在一个实施例中,本系统中可以采用完备互补正交对偶码为训练序列,其特点为自相关函数在原点是理想的冲击函数,原点以外处处为零,而互相关函数处处为零,完备互补正交对偶码的自相关特性如附图10所示。因此当训练序列重叠时也不会相互造成干扰。这样设计可以提高系统的频谱利用率和传输速率。In an embodiment, the complete complementary orthogonal dual code can be used as the training sequence in the system, which is characterized in that the autocorrelation function is an ideal impact function at the origin, where the origin is zero, and the cross-correlation function is zero, complete. The autocorrelation properties of the complementary orthogonal dual code are as shown in FIG. Therefore, when the training sequences overlap, they do not cause interference with each other. This design can improve the spectrum utilization and transmission rate of the system.
本领域技术人员将可理解,信息、信号和数据可使用各种不同技术和技艺中的任何技术和技艺来表示。例如,以上描述通篇引述的数据、指令、命令、信息、信号、位(比特)、符号、和码片可由电压、电流、电磁波、磁场或磁粒子、光场或光学粒 子、或其任何组合来表示。Those skilled in the art will appreciate that information, signals, and data may be represented using any of a variety of different technologies and techniques. For example, the data, instructions, commands, information, signals, bits (bits), symbols, and chips referenced throughout the above description may be by voltage, current, electromagnetic waves, magnetic fields or magnetic particles, light fields or optical particles. Represented by sub, or any combination thereof.
本领域技术人员将进一步领会,结合本文中所公开的实施例来描述的各种解说性逻辑板块、模块、电路、和算法步骤可实现为电子硬件、计算机软件、或这两者的组合。为清楚地解说硬件与软件的这一可互换性,各种解说性组件、框、模块、电路、和步骤在上面是以其功能性的形式作一般化描述的。此类功能性是被实现为硬件还是软件取决于具体应用和施加于整体系统的设计约束。技术人员对于每种特定应用可用不同的方式来实现所描述的功能性,但这样的实现决策不应被解读成导致脱离了本发明的范围。Those skilled in the art will further appreciate that the various illustrative logical blocks, modules, circuits, and algorithm steps described in connection with the embodiments disclosed herein may be implemented as electronic hardware, computer software, or combinations of both. To clearly illustrate this interchangeability of hardware and software, various illustrative components, blocks, modules, circuits, and steps are described above generally in the form of their functionality. Whether such functionality is implemented as hardware or software depends on the particular application and design constraints imposed on the overall system. The skilled person will be able to implement the described functionality in a different manner for each particular application, but such implementation decisions should not be interpreted as causing a departure from the scope of the invention.
结合本文所公开的实施例描述的各种解说性逻辑模块、和电路可用通用处理器、数字信号处理器(DSP)、专用集成电路(ASIC)、现场可编程门阵列(FPGA)或其它可编程逻辑器件、分立的门或晶体管逻辑、分立的硬件组件、或其设计成执行本文所描述功能的任何组合来实现或执行。通用处理器可以是微处理器,但在替换方案中,该处理器可以是任何常规的处理器、控制器、微控制器、或状态机。处理器还可以被实现为计算设备的组合,例如DSP与微处理器的组合、多个微处理器、与DSP核心协作的一个或多个微处理器、或任何其他此类配置。The various illustrative logic modules, and circuits described in connection with the embodiments disclosed herein may be general purpose processors, digital signal processors (DSPs), application specific integrated circuits (ASICs), field programmable gate arrays (FPGAs), or other programmable Logic devices, discrete gate or transistor logic, discrete hardware components, or any combination thereof designed to perform the functions described herein are implemented or executed. A general purpose processor may be a microprocessor, but in the alternative, the processor may be any conventional processor, controller, microcontroller, or state machine. The processor may also be implemented as a combination of computing devices, such as a combination of a DSP and a microprocessor, a plurality of microprocessors, one or more microprocessors in conjunction with a DSP core, or any other such configuration.
结合本文中公开的实施例描述的方法或算法的步骤可直接在硬件中、在由处理器执行的软件模块中、或在这两者的组合中体现。软件模块可驻留在RAM存储器、闪存、ROM存储器、EPROM存储器、EEPROM存储器、寄存器、硬盘、可移动盘、CD-ROM、或本领域中所知的任何其他形式的存储介质中。示例性存储介质耦合到处理器以使得该处理器能从/向该存储介质读取和写入信息。在替换方案中,存储介质可以被整合到处理器。处理器和存储介质可驻留在ASIC中。ASIC可驻留在用户终端中。在替换方案中,处理器和存储介质可作为分立组件驻留在用户终端中。The steps of a method or algorithm described in connection with the embodiments disclosed herein may be embodied in hardware, in a software module executed by a processor, or in a combination of the two. A software module may reside in RAM memory, flash memory, ROM memory, EPROM memory, EEPROM memory, registers, hard disk, a removable disk, a CD-ROM, or any other form of storage medium known in the art. An exemplary storage medium is coupled to the processor to enable the processor to read and write information to/from the storage medium. In the alternative, the storage medium can be integrated into the processor. The processor and the storage medium can reside in an ASIC. The ASIC can reside in the user terminal. In the alternative, the processor and the storage medium may reside as a discrete component in the user terminal.
在一个或多个示例性实施例中,所描述的功能可在硬件、软件、固件或其任何组合中实现。如果在软件中实现为计算机程序产品,则各功能可以作为一条或更多条指令或代码存储在计算机可读介质上或藉其进行传送。计算机可读介质包括计算机存储介质和通信介质两者,其包括促成计算机程序从一地向另一地转移的任何介质。存储介质可以是能被计算机访问的任何可用介质。作为示例而非限定,这样的计算机可读介质可包括RAM、ROM、EEPROM、CD-ROM或其它光盘存储、磁盘存储或其它磁存储设备、或能被用来携带或存储指令或数据结构形式的合意程序代码且能被计算机访问的任何其它介质。任何连接也被正当地称为计算机可读介质。例如,如果软件是使用同轴电缆、光纤电缆、双绞线、数字订户线(DSL)、或诸如红外、无线电、以 及微波之类的无线技术从web网站、服务器、或其它远程源传送而来,则该同轴电缆、光纤电缆、双绞线、DSL、或诸如红外、无线电、以及微波之类的无线技术就被包括在介质的定义之中。如本文中所使用的盘(disk)和碟(disc)包括压缩碟(CD)、激光碟、光碟、数字多用碟(DVD)、软盘和蓝光碟,其中盘(disk)往往以磁的方式再现数据,而碟(disc)用激光以光学方式再现数据。上述的组合也应被包括在计算机可读介质的范围内。In one or more exemplary embodiments, the functions described may be implemented in hardware, software, firmware, or any combination thereof. If implemented as a computer program product in software, the functions may be stored on or transmitted as one or more instructions or code on a computer readable medium. Computer readable media includes both computer storage media and communication media including any medium that facilitates transfer of a computer program from one place to another. A storage medium may be any available media that can be accessed by a computer. By way of example and not limitation, such computer readable media may comprise RAM, ROM, EEPROM, CD-ROM or other optical disk storage, disk storage or other magnetic storage device, or can be used to carry or store instructions or data structures. Any other medium that is desirable for program code and that can be accessed by a computer. Any connection is also properly referred to as a computer readable medium. For example, if the software is using coaxial cable, fiber optic cable, twisted pair, digital subscriber line (DSL), or such as infrared, radio, And wireless technologies such as microwaves are transmitted from web sites, servers, or other remote sources, such as coaxial cable, fiber optic cable, twisted pair, DSL, or wireless technologies such as infrared, radio, and microwave. It is included in the definition of the medium. Disks and discs as used herein include compact discs (CDs), laser discs, optical discs, digital versatile discs (DVDs), floppy discs, and Blu-ray discs, in which disks are often reproduced magnetically. Data, and discs optically reproduce data with a laser. Combinations of the above should also be included within the scope of computer readable media.
提供对本公开的先前描述是为使得本领域任何技术人员皆能够制作或使用本公开。对本公开的各种修改对本领域技术人员来说都将是显而易见的,且本文中所定义的普适原理可被应用到其他变体而不会脱离本公开的精神或范围。由此,本公开并非旨在被限定于本文中所描述的示例和设计,而是应被授予与本文中所公开的原理和新颖性特征相一致的最广范围。 The previous description of the disclosure is provided to enable any person skilled in the art to make or use the disclosure. Various modifications to the present disclosure will be obvious to those skilled in the art, and the general principles defined herein may be applied to other variations without departing from the spirit or scope of the disclosure. The present disclosure is not intended to be limited to the examples and designs described herein, but rather the broadest scope of the principles and novel features disclosed herein.

Claims (30)

  1. 一种信号处理方法,包括:A signal processing method includes:
    对接收信号执行预处理,所述接收信号包括基于完备互补正交对偶码的训练序列,所述执行预处理包括:Performing pre-processing on the received signal, the received signal comprising a training sequence based on a complete complementary orthogonal dual code, the performing pre-processing comprising:
    采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行预处理。Preprocessing is performed on the received signal by using the training sequence based on the complete complementary orthogonal dual code.
  2. 如权利要求1所述的信号处理方法,其特征在于,所述训练序列频宽大于数据频宽且训练序列的功率谱密度低于数据的功率谱密度The signal processing method according to claim 1, wherein the training sequence bandwidth is greater than the data bandwidth and the power spectral density of the training sequence is lower than the power spectral density of the data.
  3. 如权利要求1或2所述的信号处理方法,其特征在于,所述完备互补正交对偶码包括LAS码。The signal processing method according to claim 1 or 2, wherein said complete complementary orthogonal dual code comprises a LAS code.
  4. 如权利要求1或2所述的信号处理方法,其特征在于,所述采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行预处理包括以下至少之一:The signal processing method according to claim 1 or 2, wherein said performing preprocessing on said received signal using said training sequence based on a complete complementary orthogonal dual code comprises at least one of the following:
    采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行定时同步;Performing timing synchronization on the received signal by using the training sequence based on the complete complementary orthogonal dual code;
    采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行载波同步;或Performing carrier synchronization on the received signal using the training sequence based on the complete complementary orthogonal dual code; or
    采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行信道估计。Channel estimation is performed on the received signal using the training sequence based on the complete complementary orthogonal dual code.
  5. 如权利要求4所述的信号处理方法,其特征在于,执行信道估计包括:The signal processing method according to claim 4, wherein performing channel estimation comprises:
    检测接收信号中的训练序列;以及Detecting a training sequence in the received signal;
    对基于本地训练序列的第一矩阵与基于接收信号中训练序列的第二矩阵执行矩阵运算以获得信道估计值。A matrix operation is performed on the first matrix based on the local training sequence and the second matrix based on the training sequence in the received signal to obtain a channel estimate.
  6. 如权利要求5所述的信号处理方法,其特征在于,利用最小二乘法对所述第一矩阵和所述第二矩阵执行所述矩阵运算。The signal processing method according to claim 5, wherein said matrix operation is performed on said first matrix and said second matrix by a least squares method.
  7. 如权利要求6所述的信号处理方法,其特征在于,所述第一矩阵的列数等于信道的多径数目,所获得的信道估计值为多径信道估计值。The signal processing method according to claim 6, wherein the number of columns of the first matrix is equal to the number of multipaths of the channel, and the obtained channel estimation value is a multipath channel estimation value.
  8. 如权利要求4所述的信号处理方法,其特征在于,检测接收信号中的训练序列是通过使用滑窗法将接收信号与本地的训练序列执行自相关 运算并检测自相关峰值来进行的。The signal processing method according to claim 4, wherein detecting the training sequence in the received signal is performing autocorrelation of the received signal with the local training sequence by using a sliding window method Operate and detect autocorrelation peaks.
  9. 如权利要求4所述的信号处理方法,其特征在于,执行载波同步包括:The signal processing method according to claim 4, wherein performing carrier synchronization comprises:
    将接收信号中的训练序列与本地的训练序列执行互相关运算,以获得互相关结果;Performing a cross-correlation operation on the training sequence in the received signal and the local training sequence to obtain a cross-correlation result;
    将所述互相关结果与所述互相关结果的延迟版本执行互相关运算以获得接收端与发射端之间的频偏;以及Performing a cross-correlation operation on the cross-correlation result and the delayed version of the cross-correlation result to obtain a frequency offset between the receiving end and the transmitting end;
    基于所述频偏对所述接收信号执行频偏校正。Frequency offset correction is performed on the received signal based on the frequency offset.
  10. 如权利要求9所述的信号处理方法,其特征在于,还包括:The signal processing method according to claim 9, further comprising:
    先将所述接收信号解调至基带,以用于后续的所述互相关运算。The received signal is first demodulated to baseband for subsequent cross-correlation operations.
  11. 如权利要求9所述的信号处理方法,其特征在于,所述接收信号中的训练序列还被用于定时同步,所述训练序列的位置是基于定时同步的结果来确定的。The signal processing method according to claim 9, wherein the training sequence in said received signal is further used for timing synchronization, and the position of said training sequence is determined based on a result of timing synchronization.
  12. 如权利要求4所述的信号处理方法,其特征在于,所述采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行预处理包括:通过基于训练序列的自相关运算和自相关峰值检测来执行定时同步。The signal processing method according to claim 4, wherein said performing preprocessing on said received signal using said training sequence based on a complete complementary orthogonal dual code comprises: performing autocorrelation operation based on training sequence and self Correlated peak detection to perform timing synchronization.
  13. 如权利要求4所述的信号处理方法,其特征在于,所述采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行预处理包括:通过基于训练序列的互相关运算来执行载波同步。The signal processing method according to claim 4, wherein said performing preprocessing on said received signal using said training sequence based on a complete complementary orthogonal dual code comprises: performing a cross correlation operation based on a training sequence Carrier synchronization.
  14. 如权利要求4所述的信号处理方法,其特征在于,所述采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行预处理包括:通过基于训练序列的最小二乘法运算来执行信道估计。The signal processing method according to claim 4, wherein said performing preprocessing on said received signal using said training sequence based on a complete complementary orthogonal dual code comprises: performing a least squares operation based on a training sequence Perform channel estimation.
  15. 如权利要求4所述的信号处理方法,其特征在于,所述信号处理方法被应用于OvTDM系统、OvFDM系统、OvCDM系统、OvSDM系统、或OvHDM系统。The signal processing method according to claim 4, wherein the signal processing method is applied to an OvTDM system, an OvFDM system, an OvCDM system, an OvSDM system, or an OvHDM system.
  16. 一种信号处理装置,包括:A signal processing device comprising:
    预处理单元,用于对接收信号执行预处理,所述接收信号包括基于完备互补正交对偶码的训练序列,所述预处理单元采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行预处理。 a pre-processing unit, configured to perform pre-processing on the received signal, where the received signal includes a training sequence based on a complete complementary orthogonal dual code, and the pre-processing unit uses the training sequence based on the complete complementary orthogonal dual code to The received signal performs preprocessing.
  17. 如权利要求16所述的信号处理装置,其特征在于,训练序列频宽大于数据频宽且训练序列的功率谱密度低于数据的功率谱密度。The signal processing apparatus according to claim 16 wherein the training sequence bandwidth is greater than the data bandwidth and the power spectral density of the training sequence is lower than the power spectral density of the data.
  18. 如权利要求16或17所述的信号处理装置,其特征在于,所述完备互补正交对偶码包括LAS码。A signal processing apparatus according to claim 16 or 17, wherein said complete complementary orthogonal dual code comprises a LAS code.
  19. 如权利要求16或17所述的信号处理装置,其特征在于,所述预处理单元包括以下至少之一:The signal processing device according to claim 16 or 17, wherein the preprocessing unit comprises at least one of the following:
    定时同步单元,采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行定时同步;a timing synchronization unit, configured to perform timing synchronization on the received signal by using the training sequence based on a complete complementary orthogonal dual code;
    载波同步单元,采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行载波同步;或a carrier synchronization unit that performs carrier synchronization on the received signal by using the training sequence based on a complete complementary orthogonal dual code; or
    信道估计单元,采用所述基于完备互补正交对偶码的训练序列对所述接收信号执行信道估计。And a channel estimation unit that performs channel estimation on the received signal by using the training sequence based on the complete complementary orthogonal dual code.
  20. 如权利要求19所述的信号处理装置,其特征在于,信道估计包括:检测接收信号中的训练序列;以及The signal processing device according to claim 19, wherein the channel estimation comprises: detecting a training sequence in the received signal;
    对基于本地训练序列的第一矩阵与基于接收信号中训练序列的第二矩阵执行矩阵运算以获得信道估计值。A matrix operation is performed on the first matrix based on the local training sequence and the second matrix based on the training sequence in the received signal to obtain a channel estimate.
  21. 如权利要求20所述的信号处理装置,其特征在于,利用最小二乘法对所述第一矩阵和所述第二矩阵执行所述矩阵运算。A signal processing apparatus according to claim 20, wherein said matrix operation is performed on said first matrix and said second matrix by a least squares method.
  22. 如权利要求21所述的信号处理方法,其特征在于,所述第一矩阵的列数等于信道的多径数目,所获得的信道估计值为多径信道估计值。The signal processing method according to claim 21, wherein the number of columns of the first matrix is equal to the number of multipaths of the channel, and the obtained channel estimation value is a multipath channel estimation value.
  23. 如权利要求20所述的信号处理装置,其特征在于,检测接收信号中的训练序列是通过使用滑窗法将接收信号与本地的训练序列执行自相关运算并检测自相关峰值来进行的。The signal processing apparatus according to claim 20, wherein detecting the training sequence in the received signal is performed by performing an autocorrelation operation on the received signal and the local training sequence using a sliding window method and detecting the autocorrelation peak.
  24. 如权利要求20所述的信号处理装置,其特征在于,执行载波同步包括:将接收信号中的训练序列与本地的训练序列执行互相关运算,以获得互相关结果;The signal processing apparatus according to claim 20, wherein performing carrier synchronization comprises: performing a cross-correlation operation on the training sequence in the received signal and the local training sequence to obtain a cross-correlation result;
    将所述互相关结果与所述互相关结果的延迟版本执行互相关运算以获 得接收端与发射端之间的频偏;以及Performing a cross-correlation operation on the cross-correlation result and the delayed version of the cross-correlation result to obtain The frequency offset between the receiving end and the transmitting end;
    基于所述频偏对所述接收信号执行频偏校正。Frequency offset correction is performed on the received signal based on the frequency offset.
  25. 如权利要求23所述的信号处理装置,其特征在于,还包括:The signal processing device of claim 23, further comprising:
    先将所述接收信号解调至基带,以用于后续的所述互相关运算。The received signal is first demodulated to baseband for subsequent cross-correlation operations.
  26. 如权利要求23所述的信号处理装置,其特征在于,所述接收信号中的训练序列还被用于定时同步,所述训练序列的位置是基于定时同步的结果来确定的。The signal processing apparatus according to claim 23, wherein the training sequence in said received signal is further used for timing synchronization, and the position of said training sequence is determined based on a result of timing synchronization.
  27. 如权利要求19所述的信号处理装置,其特征在于,所述预处理单元包括所述定时同步单元,所述定时同步单元通过基于训练序列的自相关运算和自相关峰值检测来执行定时同步。The signal processing apparatus according to claim 19, wherein said pre-processing unit includes said timing synchronization unit, said timing synchronization unit performing timing synchronization by an autocorrelation operation based on a training sequence and autocorrelation peak detection.
  28. 如权利要求19所述的信号处理装置,其特征在于,所述预处理单元包括所述载波同步单元,所述载波同步单元通过基于训练序列的互相关运算来执行载波同步。The signal processing apparatus according to claim 19, wherein said pre-processing unit comprises said carrier synchronization unit, and said carrier synchronization unit performs carrier synchronization by a cross-correlation operation based on a training sequence.
  29. 如权利要求19所述的信号处理装置,其特征在于,所述预处理单元包括所述信道估计单元,所述信道估计单元通过基于训练序列的最小二乘法运算来执行信道估计。The signal processing apparatus according to claim 19, wherein said pre-processing unit comprises said channel estimation unit, said channel estimation unit performing channel estimation by a least squares operation based on a training sequence.
  30. 如权利要求16所述的信号处理装置,其特征在于,所述信号处理方法被应用于OvTDM系统、OvFDM系统、OvCDM系统、OvSDM系统、或OvHDM系统。 The signal processing device according to claim 16, wherein said signal processing method is applied to an OvTDM system, an OvFDM system, an OvCDM system, an OvSDM system, or an OvHDM system.
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