WO2018029309A1 - Procédé pour faire fonctionner un convertisseur et convertisseur fonctionnant de manière correspondante - Google Patents

Procédé pour faire fonctionner un convertisseur et convertisseur fonctionnant de manière correspondante Download PDF

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Publication number
WO2018029309A1
WO2018029309A1 PCT/EP2017/070353 EP2017070353W WO2018029309A1 WO 2018029309 A1 WO2018029309 A1 WO 2018029309A1 EP 2017070353 W EP2017070353 W EP 2017070353W WO 2018029309 A1 WO2018029309 A1 WO 2018029309A1
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WO
WIPO (PCT)
Prior art keywords
switching frequency
current
motor current
motor
switching
Prior art date
Application number
PCT/EP2017/070353
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German (de)
English (en)
Inventor
Marco BOHLLÄNDER
Original Assignee
Valeo Siemens Eautomotive Germany Gmbh
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Valeo Siemens Eautomotive Germany Gmbh filed Critical Valeo Siemens Eautomotive Germany Gmbh
Publication of WO2018029309A1 publication Critical patent/WO2018029309A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H02P27/085—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation wherein the PWM mode is adapted on the running conditions of the motor, e.g. the switching frequency

Definitions

  • the invention relates to a method for operating a power converter of an electric machine, in particular for an electrically driven motor vehicle, comprising a Brü ⁇ bridge circuit with a number of semiconductor switches and with an intermediate circuit capacitor. It further relates to a working according to this method power converter and an electric machine with such a power converter.
  • Electric (electric motor) driven vehicles such as electric or hybrid vehicles, have ty ⁇ pically electric machines for driving one or both motor vehicle axles.
  • electromotive drive machines usually include a controlled synchronous or asynchronous motor as an electric motor, which is coupled to the supply of electrical energy to an in-vehicle energy storage (high-voltage battery).
  • the electric motor of the electrical machine conventionally comprises a stator relative to a rotatably mounted ro tor, which is by means of a rotating magnetic field is trie ⁇ ben.
  • the coil windings (phase windings, stator windings) of the stator are acted upon by a corresponding three-phase current (alternating voltage) as motor current, which is converted from a DC voltage or from a direct current (input current) of the energy accumulator by means of a power converter.
  • such power converters are suitable and configured to convert the input current of the energy store into the motor current as inverter (inverter) in normal operation of the machine.
  • the power converters are generally suitable and set up to convert a generated motor current of the electric motor into a direct current (regenerative current) for feeding into the energy store in a regenerative or recuperative operation as a rectifier.
  • the power converter has a bridge circuit coupled to an intermediate circuit capacitor (intermediate circuit, commutation circuit).
  • the bridge circuit comprises a number of (motor) phases corresponding number of bridge modules (half bridges, power module, commutation ⁇ cell) with semiconductor switches, which are connected between an outgoing line and a return line of the converter.
  • the power converter is connected to the power supply by means of supply lines.
  • supply lines For high power or high currents, such as occur ⁇ bil Scheme example in Automo, due to the (re) of the semiconductor switch (over-) are spikes and (chipboard ubens-) oscillations testimony published in the lines of the inverter switching.
  • These interference voltages are typically based ei ⁇ nes voltage mean and peak-to-peak voltage relationship be ⁇ as a voltage amplitude, the so-called
  • the main influences on the ripple voltage are the average motor current, which essentially means the RMS value (root mean square) of the generated three-phase current, as well as the flux and torque-forming components characterizing the motor current.
  • these components are essentially described by a d-current component and a q-current component in the course of a vector control.
  • the modulation ⁇ influenced degree, which means degree of triggering the semiconductor switch, which occurs ripple. This means that the Ripp ⁇ read voltage is dependent on the current operating state of the electric motor and thus of the current operating state of the converter.
  • the DC link capacitor acts by means of its capacity as an additional influencing variable on the ripple voltage.
  • the capacitance has a damping effect on the amplitude of the ripple voltage, which means that the ripple amplitude is reduced by the DC link capacitor.
  • the higher the capacity the lower the voltage occurring Ripplespan ⁇ .
  • Another important factor is the (Um-) switching frequency of the semiconductor switch (clock frequency), that means the PWM (pulse width modulation) controlled, ge ⁇ clocked switching the semiconductor switch (PWM control).
  • the switching frequency is fixed and the ⁇ art chosen such that the frequency of the fundamental oscillation of the motor current does not exceed a switching frequency-dependent threshold value at a maximum speed of Elektromo ⁇ tors (full load).
  • the switching frequency is chosen only as high as at least necessary because (re) switching losses of the semiconductor switches for higher switching frequencies increase. Thus, the overall efficiency and the maximum output power of the electric machine are limited.
  • the capacitance of the intermediate circuit capacitor in such a way to dimen ⁇ sionieren that a maximum current (maximum value) in the overall selected (fixed) switching frequency of the semiconductor switch in any operating point, that is, not even during a high or full load operation from which motor current is exceeded.
  • the portrait or full load operation usually occurs depending ⁇ but oversized only in certain situations, such as in an acceleration process, whereby the DC link capacitor, the (frequent) Normal operation of the electrical machine.
  • the intermediate circuit capacitor has a considerable capacity component (buffer) for the rarely occurring, high motor currents or ripple voltages.
  • the construction costs and the installation space of the power converter are disadvantageously increased.
  • the value of the maximum current is chosen, for example at hand ⁇ a statistical distribution of the power level of the motor current over a service life of the converter.
  • the capacitance of the DC link capacitors is the gate, for example, dimensioned such that this (sta ⁇ tical) maximum value satisfies the allowable values of the Ripplespan- voltage.
  • the invention has the object of providing a ge possible ⁇ One suitable method for operating a power converter suits ⁇ ben.
  • the process is to a use of an intermediate circuit capacitor of the converter with the lowest possible capacitance value, while maintaining a high, reliable as possible motor current ermögli ⁇ chen.
  • the invention is further based on the object of specifying a power converter operated by such a method and an electric machine having such a power converter.
  • the object is achieved according to the invention with the features of claim 1.
  • the stated object with the features of claim 9 and with regard to an electric machine having the power converter with the features of claim 10 is achieved according to the invention.
  • Advantageous embodiments and Wei ⁇ educations are the subject of the respective subclaims.
  • the inventive method is suitable for operating a power ⁇ judge an electric machine and is rich ⁇ tet.
  • the electric machine is in this case for example part of an electrically operated motor vehicle, such as a hybrid or electric vehicle.
  • the power converter for example, as a removable ⁇ converter (inverter) executed has a bridge circuit with a number of semiconductor switches and with an intermediate circuit capacitor.
  • ⁇ current to a maximum value (maximum current) is set, and the switching frequency is increased for the switching of the semiconductor switch for a limited period of time.
  • a high-load operation is in this case an engine operating To Hide ⁇ hen, wherein an increased ripple voltage is generated which is not sufficiently reduced circuit capacitor by the capacitance of the intermediate.
  • the motor current is thus set during the high load operation by means of a time-limited increase in the switching frequency to the maximum value. This signified tet ⁇ that the switching frequency for the machine operation is not fixed or fixed but is varied dynamically between Nor ⁇ malwholesome and high-load operation. In other words, the switching frequency is increased depending on the operating point of the electric machine or the electric motor.
  • the switching frequency is increased as a function of the motor current generated by the bridge circuit.
  • the switching frequency is readjusted or tracked as a function of the output-side motor current.
  • a reliable and reliable increase in the switching frequency affords.
  • between the motor current during normal operation and the maximum value of the motor current during the high-load operation before ⁇ is preferably defines a number of current thresholds. at a setting of the motor current at the maximum value by ⁇ the value of the motor current thus passes successively through the various ver ⁇ Motorschwell tone, wherein the switching frequency is increased, when the motor current reaches such a current threshold or exceeds.
  • the time period is determined based on an operating temperature of the or each semiconductor switch.
  • a junction temperature of the semiconductor switches is used as a measure of the operating temperature.
  • the operating temperature is determined based on a stored thermal model of the semiconductor switches.
  • the actual value of the operating or junction temperature for self-protection and limiting is here in a pre ⁇ given time frame, for example in a Millise Hras ⁇ ter periodically determined purposes.
  • the heat development due to the switching losses is itself dependent on the operating temperature.
  • the heat development is coupled, which means that higher switching losses occur at higher temperatures, which increases the heat development.
  • the operating temperature is compared with a temperature threshold in a particularly reliable training. When the operating temperature reaches or exceeds the temperature threshold, the motor current is reduced and / or limited. This corresponds to the end of the time period.
  • the period begins with the harnessbe- drove conditional increase of the motor current and ends by reaching the temperature threshold of the calculated Be ⁇ operating temperature due to the increased motor current and increased switching frequency.
  • This corresponds to a time limitation of the overload operation of the semiconductor switches for their protection (self-protection).
  • the motor current is set to a value reduced with respect to the maximum value. In other words, there is a current limitation of the motor current. As a result, the switching losses are reduced, so that the operating temperature is reduced ver ⁇ .
  • An additional or further aspect of the method according to the invention provides that the switching frequency during the high load operation in stages, that is in discrete Fre ⁇ quenz suitsen set. As a result, a simple adjustment of the switching frequency is realized.
  • the switching frequency is gradually increased during the high load operation, when the Mo ⁇ gate current falls below the predetermined maximum value or does not exceed the operating temperature ⁇ turschwellwert below the temperature exceeds or not. Additionally or alternatively, the switching frequency during the high load operation is gradually reduced when the motor ⁇ current reaches or falls below the maximum value reduced current threshold. The reduced
  • An inventive converter is suitable for the reliable operation of an electrical machine and set up.
  • the power converter has a controller, which means a control unit, on.
  • the controller is in this case generally - program and / or circuitry - set up to carry out the inventive method described above.
  • the controller is thus specifically directed to be ⁇ set during high-load operation of the motor current to a maximum value and the switching frequency of the semiconductor switches for redirecting switch to increase.
  • the controller is adapted and arranged to adjust or track the Wegfre acid sequence depending on the motor current generated.
  • the controller is formed at least in the core by a microcontroller with a processor and a data memory in which the functionality for performing the method according to the invention in the form of operating software (firmware) is implemented by programming, so that the method - optionally in interaction with a Vehicle user - is performed automatically when running the operating software in the microcontroller.
  • the controller may be alternatively but an ASIC (application-specific integrated circuit) formed in the framework of the invention by a non-programmable electronic component, for example, in which the functionality is implemented through ⁇ out the method according to the invention with circuitry means.
  • ASIC application-specific integrated circuit
  • the power converter operated with the method is thus essentially always designed for the point, that is, he works at any time of operation in a possible effec ⁇ tive manner without Begren ⁇ tions, in particular letension the amplitude threshold of Ripp- to exceed safety. This makes it possible to use a particularly cost-effective and space-compact intermediate circuit capacitor.
  • the power converter is installed in an electrical machine, in particular for an electrically operated motor vehicle.
  • the Stromrich ⁇ ter is suitably connected between an input side, in-vehicle energy storage, such as a high-voltage battery, and an output-side electric motor, for example, an asynchronous motor for driving one or both vehicle axles.
  • an inverter (inverter) running converter converts an input current of the energy storage in a motor current for operation of the electric motor.
  • the inverter converts the generated motor current into an input current for feeding it into the energy store.
  • the power converter operated by the method according to the invention or operating thereafter implements a reliable and cost-effective electric machine.
  • FIG. 1 shows an electrical machine with an energy store and an electric motor and a power converter connected therebetween, in simplified and schematic representations.
  • 2 shows a diagram of a desired torque of the electric motor over time
  • FIG. 6 shows a diagram of an operating temperature of the semiconductor switches over time.
  • the Ma ⁇ machine 2 in this embodiment comprises a driving ⁇ generating internal electric energy storage 4 in the form of a high-voltage battery and a motor vehicle axes antrei ⁇ inputting electric motor 6.
  • the electric motor 6 is in this case connected to the energy store by means of a power converter.
  • the power converter 8 has an outgoing line 10 a and a return line 10 b, with which the power converter 8 is connected to the energy store 4. Between the lines 10a and 10b, an intermediate circuit capacitor 12 and a bridge circuit 14 with three bridge modules (half bridges, commutation cells) 16 are connected. In the (normal) operation, a power converter 8 to the supplied input current IE of the energy accumulator 4 through the bridges ⁇ circuit 14 in a three-phase motor voltage relationship ⁇ as a three-phase current with the phases u, v, w is converted.
  • the phases u, v, w - hereinafter also referred to collectively as the motor current IM - are guided for operation of the electric motor 6 to corresponding phase or winding ends of a stator, not shown.
  • a generatie ⁇ or recuperative operation of the generated motor current IM is converted to the power converter 8 in the input current IE and fed into the energy storage 4.
  • each bridge module 16 has two semiconductor switches 20 embodied as IGBTs (insulative gate bipolar transistor).
  • the semiconductor switches 20, which are provided only by way of example with reference numerals, are clocked by means of pulse-width-modulated signals (PWM control) of a driver controlled by the control signals with a switching frequency f between a conducting and a non-conducting state. tet.
  • PWM control pulse-width-modulated signals
  • exemplary signal waveforms for the operation of the power converter 8 are shown.
  • the schematic signal curves are along a respective abscissa axis as (common) time axis t and a respective
  • the time axis t is divided into the Figu ⁇ ren in partial or six time periods ti to t6.
  • the Figures 2 to 6 show in particular the temporal Sig- nalverrise during a high-load operation, in particular currency ⁇ rend of a full load operation of the engine 2, wherein the motor current IM is set to a maximum value Imax and the switching frequency f of the switching of the semiconductor switch 20 for a Duration ⁇ during periods t2, t3 and t4 is increased.
  • FIG 2 a time characteristic of a target Drehmo ⁇ D ments of the electric motor 6 during a Bevantungsvor ⁇ path of the motor vehicle is shown.
  • the target torque D is in this case a measure of the requirement which a vehicle user places on the machine 2 or the electric motor 6 or the power converter 8 in this driving situation of the motor vehicle.
  • the FIG 3 shows the time profile of the signal generated from the input stream ⁇ IE motor current IM.
  • the motor current IM is set at full load operation to the maximum value Imax, so that the desired torque is generated by the electric motor.
  • FIG 4 the time course of the ripple voltage generated in the wires 10a and 10b by the switching operations of the semiconductor switches ⁇ R 20 is illustrated.
  • the rippling voltage R increases in the time interval ti up to an upper one
  • FIG. 5 shows the time profile of the switching frequency f, which means the clock frequency of the PWM control of the semiconductor switch 20.
  • f the switching frequency between discrete three (switching) frequency values
  • f3 the switching frequency between discrete three (switching) frequency values
  • FIG. 6 shows an operating temperature TB or a junction temperature Tss of the semiconductor switch 20.
  • the temperature TB or Tss is computationally determined by the controller 18 during operation in a regular time grid.
  • a thermal model of the semiconductor switch 20 is stored in a memory of the controller 18.
  • the thermal model calculates the case Tem ⁇ peraturzuddling the semiconductor switch 20, taking into account of the switching losses, the switching losses in the Wesent ⁇ union directly proportional to the switching frequency f.
  • the electric motor 6 is operated in a normal mode.
  • the desired target torque D is constantly increasing, so that by the controller corresponding to a ⁇ acquisition of the motor current IM generated is controlled.
  • the semiconductor switches 20 are controlled pulse width modulated with a first switching frequency value fi.
  • the ripple R increases at constant frequency fi. Furthermore, the switching and conduction losses of the bridge circuit 14 are increased with increasing motor current IM. The heat generated thereby leads to an increase of the (virtual) operating temperature T B of the semiconductor switches 20.
  • the motor current IM reaches a first current threshold value Ii.
  • the ripple voltage R would be preset by the motor current I M when the current threshold value Ii is exceeded
  • Exceed amplitude threshold Ai To protect the electrical machine 2 to avoid such is exceeded, the switching frequency is f f 2 ⁇ switched by the switching frequency value fi of the this increased switching frequency value. This means that the switching frequency f is tracked to the motor ⁇ current IM. Thereby, the generated Ripplespan ⁇ voltage is reduced to a lower amplitude threshold A2. The motor current IM is further increased, which caused by the hung Erhö- of motor current and the switching frequency f a white ⁇ tere increase in operating temperature TB relationship ⁇ as is expected.
  • the motor current IM exceeds a second current threshold value I2.
  • the current threshold I2 is the ⁇ art dimensioned such that the ripple R in the switching frequency f ⁇ 2 would reach the amplitude threshold Ai. In this case, the switching frequency f becomes the next higher one Switching frequency f3 tracked so that the ripple voltage R is again reduced to the amplitude threshold A2.
  • the operating temperature B of the semiconductor switch 20 is further increased.
  • the motor current IM be assisted by the current I2 ⁇ threshold to the maximum value Imax, for generating the necessary under full load target torque D represents.
  • F at the maximum value Imax of the motor current IM and the switching frequency value f3 of the switching frequency ripple voltage ⁇ R is set to a voltage value smaller than the Amplitu ⁇ denschwellwert Ai limited. This means that the ripple voltage ⁇ R drove the amplitude threshold Ai both Normalbe- and during a full load operation always falls short ⁇ or not exceed.
  • the controller 18 compares the calculated value of the operating temperature T B with the temperature threshold value T ma x in the time interval of the temperature value determination.
  • the temperature threshold Tmax is determined, for example, on the basis of a characteristic curve and / or from the production data of the semiconductor switches 20.
  • the operating temperature B reaches the temperature threshold T ma x. Then reduces the
  • Controller 18 during the following period ts the Mo ⁇ torstrom IM of the maximum value Imax on the current threshold ⁇ 2.
  • the ripple voltage R is reduced to the amplitude threshold value A2.
  • the Wegfre acid sequence f is changed ⁇ switched during the time period t6 from the Wegfre ⁇ quenzwert f3 to the lower switching frequency value f 2.
  • the motor current IM is continuously increased and the switching frequency f is increased stepwise during the time period ⁇ .
  • the semiconductor switches 20 in the course of full load operation, in particular during the period ⁇ , at least partially operated in overload.
  • the increase or the switching between the switching frequency values f i, f 2 and f 3 occurs in this case, taking into account or in Ab ⁇ dependence of the motor current IM.
  • the switching frequency is f ⁇ tracked to the motor current IM, that is, switching between the switching frequency values f i, f 2 and f 3 occurs, when the motor current IM reaches the predetermined Stromschwell ⁇ values Ii or I 2, or exceeds.
  • three motor current areas Bi, B2 and B3 are defi ned ⁇ in the embodiment according to Figures 2 to the 6th
  • the motor current areas Bi, B2 and B3 are (separates ge ⁇ ) through the current threshold values Ii and I2 distinguished from each other.
  • each of these motor current ranges is Bi, B2 and E is a corresponding (operating) switching frequency ⁇ assigns> 3 f supplied.
  • the motor current range Bi corresponds to the normal operating state in which the semiconductor switches 20 having the switching frequency value fi are operated by the PWM drive.
  • the motor current ranges B2 and B3 correspond to the
  • Tracking or readjustment of the switching frequency f takes place during full-load operation in particular such that the ripple voltage R is always limited to a voltage range between the amplitude threshold values Ai and A2.
  • the current threshold values Ii and I2 of the motor current IM ⁇ are selected such that the ripple R in the respective switching frequency value fi, f 2 or f 3 the threshold amplitude Ai always falls below or does not exceed.
  • the hysteresis range H defined by the amplitude threshold values Ai and A2 is in this case dimensioned such that the capacitance of the DC link capacitor 12 is sufficient to smooth the ripple voltage R. This means that the amplitude of the ripple voltage R is substantially completely reduced by the DC link capacitor 12.
  • the motor current IM is set to the maximum value Imax.
  • the switching frequency f ⁇ is tracked by the switching frequency value fi of normal operation to the increased switching frequency f3 value of full load operation. Due to the increased motor current IM and the tracked higher switching frequency f, the switching losses during the period ⁇ of the semiconductor switch 20 to.
  • the temperature threshold value Tmax which is controlled in the series of motor current IM to the low ⁇ ren current threshold I2 or limited. If the motor current IM reaches or falls below the
  • the switching frequency f is tracked and thus from the switching frequency value f3 to the Wegfre ⁇ quenzwert f. 2 reduced. As a result, the switching and conduction losses of the semi ⁇ conductor switches 20 are reduced, whereby the value of the operating temperature T B decreases. Thereby, it is possible to re-adjust the motor current IM from the current threshold I2 to the maximum value Imax, the switching frequency f is adjusted by the switching frequency value f 2 at the switching frequency value f3.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

Lors du fonctionnement d'un convertisseur (8) d'une machine électrique (2), comprenant un montage en pont (14) qui présente un certain nombre d'interrupteurs à semi-conducteur (20) et un condensateur de circuit intermédiaire (12), le fonctionnement normal de la machine (2) s'accompagne, par une commutation des interrupteurs à semi-conducteur (20) à une fréquence de commutation (f), d'un courant d'entrée (IE) à un courant moteur (IM) pour un moteur électrique (6), alors que lors d'un fonctionnement à haut régime de la machine (2), le courant moteur (IM) est réglé à une valeur maximale (Imax) et la fréquence de commutation (f) pour la commutation des interrupteurs à semi-conducteur (20) est augmentée pendant un intervalle de temps (τ).
PCT/EP2017/070353 2016-08-11 2017-08-10 Procédé pour faire fonctionner un convertisseur et convertisseur fonctionnant de manière correspondante WO2018029309A1 (fr)

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DE102016215008.1A DE102016215008A1 (de) 2016-08-11 2016-08-11 Verfahren zum Betreiben eines Stromrichters sowie danach arbeitender Stromrichter
DE102016215008.1 2016-08-11

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CN115951192B (zh) * 2023-03-09 2023-06-23 长沙丹芬瑞电气技术有限公司 一种功率器件的结温检测装置、方法及介质

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE4330537A1 (de) * 1993-09-09 1995-03-16 Bosch Gmbh Robert Frequenzumrichter und Verfahren zu seinem Betrieb
WO2004062082A1 (fr) * 2002-12-20 2004-07-22 Siemens Aktiengesellschaft Procede de regulation d'un entrainement electrique

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP4798075B2 (ja) * 2007-06-26 2011-10-19 トヨタ自動車株式会社 モータ駆動システム
JP5408136B2 (ja) * 2008-09-11 2014-02-05 株式会社安川電機 インバータ装置、インバータコントロールシステム、モータ制御システム、インバータ装置の制御方法
JP5035641B2 (ja) * 2009-11-30 2012-09-26 アイシン・エィ・ダブリュ株式会社 電動機駆動装置の制御装置
JP2012135119A (ja) * 2010-12-21 2012-07-12 Sumitomo Heavy Ind Ltd インバータ装置
WO2012144019A1 (fr) * 2011-04-19 2012-10-26 トヨタ自動車株式会社 Dispositif de commande de convertisseur élévateur
DE102013111638A1 (de) * 2013-10-22 2015-04-23 Jungheinrich Aktiengesellschaft Flurförderzeug mit einem Fahrgeschwindigkeitsgeber

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE4330537A1 (de) * 1993-09-09 1995-03-16 Bosch Gmbh Robert Frequenzumrichter und Verfahren zu seinem Betrieb
WO2004062082A1 (fr) * 2002-12-20 2004-07-22 Siemens Aktiengesellschaft Procede de regulation d'un entrainement electrique

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
WOLFLE JULIAN ET AL: "Control Method to Increase the Reliability of IGBT Power Modules Validated on a Three Phase Inverter", 2015 IEEE VEHICLE POWER AND PROPULSION CONFERENCE (VPPC), IEEE, 19 October 2015 (2015-10-19), pages 1 - 6, XP032833915, DOI: 10.1109/VPPC.2015.7352918 *

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